Conductive inductance type multiphase voltage stabilizer and control circuit thereof

Abstract

The invention discloses a conduction inductance type multiphase voltage stabilizer and a control circuit thereof. The control circuit comprises a first current sensor, a second current sensor, a current comparator, a summator, a controller 1, a controller 2, four switching tubes and an alternating current circuit. The voltage stabilizer comprises an input power supply, 2N switching tubes, N coupling inductors, a compensation inductor, an output capacitor and an output resistor. Secondary windings of the N coupling inductors and a primary winding of the compensation inductor are connected in series to build a bridge, the control circuit changes the secondary winding of the compensation inductor to generate induced voltage on the primary winding of the compensation inductor, influences the state of the bridge, changes equivalent self-inductance values and equivalent mutual inductance values of the N coupling inductors, reduces current ripples when the voltage stabilizer is in a steady state, and improves the stability of the voltage stabilizer. And the transient response speed of the voltage stabilizer is improved.

Description

Technical Field

[0001] The present invention relates to the technical field of voltage stabilizers, and in particular to a conductive inductor multi-phase voltage stabilizer and a control circuit thereof. Background Art

[0002] The number of transistors integrated on a chip doubles every two years, which makes the requirements of microprocessor power supply systems increasingly higher, such as low voltage (<1V), high current (>800A), high efficiency, extremely high voltage accuracy under transient conditions, low cost and small size.

[0003] There is a conflict between the transient performance and steady-state performance design of the regulator, that is, if you want to improve the transient response speed, you must reduce the inductance to increase the current change rate, but smaller inductance means larger current ripple.

[0004] Therefore, how to provide a solution to the above problems is a problem that those skilled in the art need to solve at present. Summary of the invention

[0005] In order to solve the above technical problems, the present invention discloses a control circuit of a conductive inductor multi-phase voltage regulator, which includes: a first current sensor, a second current sensor, a current comparator, an adder, a controller 1 and a controller 2, four switch tubes, and an AC circuit. The voltage regulator includes: an input power supply, 2N switch tubes, N coupled inductors, a compensation inductor, an output capacitor, and an output resistor. The secondary windings of the N coupled inductors and the primary windings of the compensation inductors are connected in series to build a bridge. The control circuit generates an induced voltage in the primary winding of the compensation inductor by changing the secondary winding of the compensation inductor, thereby affecting the state of the bridge, changing the equivalent self-inductance and equivalent mutual inductance of the N coupled inductors, reducing the current ripple of the voltage regulator in steady state, and improving the response speed of the voltage regulator in transient state.

[0006] The present invention provides a control circuit of a conductive inductor multi-phase voltage stabilizer, comprising: a first current sensor, a second current sensor, a current comparator, an adder, a controller 1 and a controller 2, four switch tubes, and an AC circuit;

[0007] The switch tube is a field effect tube, the first end of the switch tube is the drain of the field effect tube, the second end of the switch tube is the source of the field effect tube, and the third end of the switch tube is the gate of the field effect tube;

[0008] The four switch tubes include an H-bridge switch tube C1, an H-bridge switch tube C2, an H-bridge switch tube C3, and an H-bridge switch tube C4;

[0009] The first terminal of the first current sensor and the compensation primary winding (N c ) is connected to the first end;

[0010] The second end of the first current sensor is connected to the first end of the current comparator;

[0011] The third terminal of the first current sensor is connected to the first terminal of the adder;

[0012] The second end of the current comparator is connected to the first end of the controller 1;

[0013] The third terminal of the current comparator is connected to the third terminal of the controller 2;

[0014] The third end of the H-bridge switch tube C1 at the second end of the controller 1, the third end of the H-bridge switch tube C4, and the fourth end of the AC circuit are connected;

[0015] The first end of the controller 2, the third end of the controller 1 and the third end of the adder are connected;

[0016] The second end of the controller 2 is connected to the third end of the H-bridge switch tube C2, the third end of the H-bridge switch tube C3, and the third end of the AC circuit;

[0017] The first end of the second current sensor is connected to the first end of the AC circuit, the first end of the H-bridge switch tube C1, and the first end of the H-bridge switch tube C2;

[0018] The second end of the second current sensor is connected to the second end of the adder;

[0019] The second end of the H-bridge switch tube C1 and the first end of the H-bridge switch tube C3, the compensation secondary winding (N x ) is connected to the first end;

[0020] The second end of the H-bridge switch tube C2 and the first end of the H-bridge switch tube C4, the compensation secondary winding (N x ) is connected to the second end of the

[0021] The second end of the AC circuit is connected to the second end of the H-bridge switch tube C3 and the second end of the H-bridge switch tube C4;

[0022] The first current sensor detects the current i on the bridge c ;

[0023] The second current sensor detects the compensating secondary winding (N x ) of the current i x ;

[0024] The current comparator receives the signal of the first current sensor, when the current i c The value satisfies the equation i c >|1.3×icpp / 2|, the output signal is sent to controller 2. When the equation is not satisfied, the output signal is sent to controller 1.

[0025] The adder converts the current i c and current i x The difference e is sent to the controller 1 and the controller 2;

[0026] The controller 1 receives the signal of the current comparator and the signal of the adder, and outputs signals to the AC circuit, the H-bridge switch tube C1 and the H-bridge switch tube C4;

[0027] The controller 2 receives the signal of the current comparator and the signal of the adder, and outputs signals to the AC circuit, the H-bridge switch tube C2 and the H-bridge switch tube C3;

[0028] The AC circuit cooperates with the four switching tubes to generate the required AC current;

[0029] Among them, |1.3×i cpp / 2| is the current i c The absolute value of the steady-state peak-to-peak value leaving a 30% margin.

[0030] Optionally, after a transient occurs in the conductive inductor multi-phase regulator, the current comparator i cpp The value of i is the new steady state cpp value;

[0031] Preferably, the current comparator can be implemented in a digital signal control system such as DSP, FPGA, etc.

[0032] Optionally, a conductive inductor multi-phase regulator using a control circuit of a conductive inductor multi-phase regulator includes: an input power supply (V in ), 2N switch tubes (S1~S N 、Q1~Q N ), N coupled inductors, compensation inductors, output capacitors (C o )、output resistance (R o );

[0033] The 2N switch tubes include N upper bridge arm switch tubes (S1-S N ) and N lower bridge arm switch tubes (Q1~Q N );

[0034] The N coupled inductors include N primary windings (N a1 ~N aN ) and N secondary windings (N b1 ~N bN );

[0035] The compensating inductor comprises a compensating primary winding (N c ) and the compensating secondary winding (N x );

[0036] The input power supply (V in ) and the positive electrode of the N upper bridge arm switch tubes (S1~S N ) is connected to the first end;

[0037] The input power supply (V in ) and the negative electrode of the N lower bridge arm switch tubes (Q1~Q N ) of the second terminal, the output capacitor (C o ) of the second end, the output resistance (R o ) is connected to the second end of the

[0038] The N primary windings (N a1 ~N aN )'s ith primary winding (N ai ) and the N upper bridge arm switch tubes (S1~S N ) of the i-th upper bridge arm switch tube (S i ) of the second end, the N lower bridge arm switch tubes (Q1~Q N )’s ith lower bridge arm switch tube (Q i ) is connected to the first end;

[0039] The N primary windings (N a1 ~N aN ) and the output resistor (R o ) first end, output capacitor (C o ) is connected to the first end;

[0040] The N secondary windings (N b1 ~N bN ) and the compensating primary winding (N c ) are connected in series;

[0041] Wherein, i=1, 2, 3...N, N≥2 and is an integer.

[0042] Optionally, the N primary windings (N a1 ~N aN )'s ith primary winding (N ai ) and the N secondary windings (N b1 ~N bN )'s ith secondary winding (N bi ) have the same name as each other;

[0043] Compensation primary winding (Nc ) and the first end of the compensating secondary winding (N x ) have the same name as each other;

[0044] Wherein, i=1, 2, 3...N, N≥2 and is an integer.

[0045] Optionally, when the controller 1 is in effect, the N coupled inductors have a first equivalent self-inductance value L self1 And the first equivalent mutual inductance value M z1 ,

[0046]

[0047] When the controller 2 is in effect, the N coupled inductors have a second equivalent self-inductance value L self2 and the second equivalent mutual inductance value M z2 ,

[0048]

[0049] The second equivalent self-inductance value is smaller than the first equivalent self-inductance value, and the second equivalent mutual inductance value is larger than the first equivalent mutual inductance value;

[0050] Where, N ≥ 2 and is an integer, La is the primary winding inductance, Lb is the secondary winding inductance, Lc is the compensated primary winding inductance, M is the mutual inductance between the primary winding and the secondary winding, M x To compensate the mutual inductance of the primary winding and the secondary winding.

[0051] Optionally, the coupling coefficient of each of the N coupled inductors is equal, and the N primary windings (N a1 ~N aN ) each primary winding has the same number of turns, and the N secondary windings (N b1 ~N bN ) each secondary winding has the same number of turns.

[0052] Compared with the prior art, the implementation of the present invention has the following beneficial effects:

[0053] The secondary windings of N coupled inductors and the primary winding of the compensation inductor are connected in series to build a bridge. The control circuit generates an induced voltage in the primary winding of the compensation inductor by changing the secondary winding of the compensation inductor, thereby affecting the state of the bridge, changing the equivalent self-inductance and equivalent mutual inductance of the N coupled inductors, reducing the current ripple of the regulator in steady state, and improving the response speed of the regulator in transient state.

[0054] It is to be understood that the foregoing general description and the following detailed description are exemplary and explanatory only and are not restrictive of the invention. BRIEF DESCRIPTION OF THE DRAWINGS

[0055] In order to more clearly illustrate the technical solutions in the embodiments of the present invention, the following briefly introduces the prior art and the drawings required for use in the embodiments. The following drawings are only some embodiments of the present invention. For ordinary technicians in this field, other drawings can be obtained based on these drawings without creative work.

[0056] Figure 1 A schematic diagram of a topological structure of a control circuit of a conductive inductor multi-phase voltage regulator of this embodiment;

[0057] Figure 2 A transient principle diagram of a control circuit of a conductive inductor multi-phase voltage regulator of this embodiment;

[0058] Figure 3 A transient principle diagram for determining a sudden increase in current in a control circuit of a conductive inductor multi-phase voltage stabilizer of the present invention;

[0059] Figure 4 A transient principle diagram for determining a sudden decrease in current of a control circuit of a conductive inductor multi-phase voltage stabilizer of the present invention;

[0060] Legend: V in For DC power supply, S1 to S N N upper bridge arm switch tubes, Q1 to Q N N lower bridge arm switch tubes, La1 to La N N primary winding inductances, Lb1 to Lb N is the inductance of N secondary windings, L c To compensate the primary winding inductance, V1, V2, ..., V N is the voltage of each phase inductor, I1, I2, ..., I N is the current of each phase inductor. DETAILED DESCRIPTION

[0061] In order to make the purpose, technical scheme and features in the embodiments of the present invention clearer, the technical scheme in the embodiments of the present invention will be clearly and completely described below in conjunction with the drawings in the embodiments of the present invention. Obviously, the described embodiments are only part of the embodiments of the present invention, not all of the embodiments. Based on the embodiments of the present invention, all other embodiments obtained by ordinary technicians in this field without creative work are within the scope of protection of the present invention.

[0062] Example 1

[0063] See also Figure 1, a schematic diagram of a topological structure of a control circuit of a conductive inductor multi-phase regulator of the present embodiment, comprising: a first current sensor, a second current sensor, a current comparator, an adder, a controller 1 and a controller 2, four switch tubes, and an AC circuit;

[0064] The switch tube is a field effect tube, the first end of the switch tube is the drain of the field effect tube, the second end of the switch tube is the source of the field effect tube, and the third end of the switch tube is the gate of the field effect tube;

[0065] The four switch tubes include an H-bridge switch tube C1, an H-bridge switch tube C2, an H-bridge switch tube C3, and an H-bridge switch tube C4;

[0066] The first terminal of the first current sensor and the compensation primary winding (N c ) is connected to the first end;

[0067] The second end of the first current sensor is connected to the first end of the current comparator;

[0068] The third terminal of the first current sensor is connected to the first terminal of the adder;

[0069] The second end of the current comparator is connected to the first end of the controller 1;

[0070] The third terminal of the current comparator is connected to the third terminal of the controller 2;

[0071] The third end of the H-bridge switch tube C1 at the second end of the controller 1, the third end of the H-bridge switch tube C4, and the fourth end of the AC circuit are connected;

[0072] The first end of the controller 2, the third end of the controller 1 and the third end of the adder are connected;

[0073] The second end of the controller 2 is connected to the third end of the H-bridge switch tube C2, the third end of the H-bridge switch tube C3, and the third end of the AC circuit;

[0074] The first end of the second current sensor is connected to the first end of the AC circuit, the first end of the H-bridge switch tube C1, and the first end of the H-bridge switch tube C2;

[0075] The second end of the second current sensor is connected to the second end of the adder;

[0076] The second end of the H-bridge switch tube C1 and the first end of the H-bridge switch tube C3, the compensation secondary winding (N x ) is connected to the first end;

[0077] The second end of the H-bridge switch tube C2 and the first end of the H-bridge switch tube C4, the compensation secondary winding (Nx ) is connected to the second end of the

[0078] The second end of the AC circuit is connected to the second end of the H-bridge switch tube C3 and the second end of the H-bridge switch tube C4;

[0079] The first current sensor detects the current i on the bridge c ;

[0080] The second current sensor detects the compensating secondary winding (N x ) of the current i x ;

[0081] The current comparator receives the signal of the first current sensor, when the current i c The value satisfies the equation i c >|1.3×i cpp / 2|, the output signal is sent to controller 2. When the equation is not satisfied, the output signal is sent to controller 1.

[0082] The adder converts the current i c and current i x The difference e is sent to the controller 1 and the controller 2;

[0083] The controller 1 receives the signal of the current comparator and the signal of the adder, and outputs signals to the AC circuit, the H-bridge switch tube C1 and the H-bridge switch tube C4;

[0084] The controller 2 receives the signal of the current comparator and the signal of the adder, and outputs signals to the AC circuit, the H-bridge switch tube C2 and the H-bridge switch tube C3;

[0085] The AC circuit cooperates with the four switching tubes to generate the required AC current;

[0086] Among them, |1.3×i cpp / 2| is the current i c The absolute value of the steady-state peak-to-peak value with a 30% margin;

[0087] The voltage regulator includes: Input power supply (V in ), 2N switch tubes (S1~S N 、Q1~Q N ), N coupled inductors, compensation inductors, output capacitors (C o )、output resistance (R o );

[0088] The 2N switch tubes include N upper bridge arm switch tubes (S1-S N ) and N lower bridge arm switch tubes (Q1~QN );

[0089] The N coupled inductors include N primary windings (N a1 ~N aN ) and N secondary windings (N b1 ~N bN );

[0090] The compensating inductor comprises a compensating primary winding (N c ) and the compensating secondary winding (N x );

[0091] The input power supply (V in ) and the positive electrode of the N upper bridge arm switch tubes (S1~S N ) is connected to the first end;

[0092] The input power supply (V in ) and the negative electrode of the N lower bridge arm switch tubes (Q1~Q N ) of the second terminal, the output capacitor (C o ) of the second end, the output resistance (R o ) is connected to the second end of the

[0093] The N primary windings (N a1 ~N aN )'s ith primary winding (N ai ) and the N upper bridge arm switch tubes (S1~S N ) of the i-th upper bridge arm switch tube (S i ) of the second end, the N lower bridge arm switch tubes (Q1~Q N )’s ith lower bridge arm switch tube (Q i ) is connected to the first end;

[0094] The N primary windings (N a1 ~N aN ) and the output resistor (R o ) first end, output capacitor (C o ) is connected to the first end;

[0095] The N secondary windings (N b1 ~N bN ) and the compensating primary winding (N c ) are connected in series;

[0096] The coupled inductor has a first equivalent self-inductance value L self1 And the first equivalent mutual inductance value M z1 , with a second equivalent self-inductance value L self2 and the second equivalent mutual inductance value M z2 ;

[0097] Wherein, i=1, 2, 3...N, N≥2 and is an integer.

[0098] In order to illustrate the benefits of the present invention, a formula will be derived below to prove that the multi-phase regulator provided by the present invention has a fast transient response.

[0099] Assume that N primary winding inductances La1~La N , N secondary winding inductances Lb1~Lb N , the mutual inductance M1~M between N primary windings and N secondary windings N The relationship between them is:

[0100]

[0101] La1~La N is the inductance value of N primary windings, Lb1~Lb N is the inductance value of N secondary windings, M1~M N is the mutual inductance between N primary windings and N secondary windings, and La, Lb, and M are their uniform values.

[0102] The N secondary winding inductances L b1 ~L bN The jth secondary winding inductance L bj The voltage on the cj :

[0103]

[0104] Among them, i c is the current on the bridge, i j is the current of the jth primary winding of the N primary windings, j=1, 2, 3...N.

[0105] Without control circuit, the primary winding N is compensated c The voltage is:

[0106]

[0107] When added to the control circuit, the primary winding N is compensated c The voltage is:

[0108]

[0109] Among them, i x The current supplied to the AC circuit, M x To compensate the mutual inductance of the primary winding and the secondary winding.

[0110] When the control circuit is not functioning:

[0111]

[0112] Let i x =i c , in steady state, keep i x =i c , and also maintain i in transient state x =i c , we can calculate down to get:

[0113] When controller 1 is in effect:

[0114]

[0115] When controller 2 is in effect:

[0116]

[0117] Among them, i y To remove the jth primary winding N aj For currents other than those specified, j=1, 2, 3…N, y=1, 2, 3…N, y≠j, and N is the number of phases of the regulator.

[0118] From the definition of coupled inductance, we can know that the equivalent self-inductance L of each phase can be obtained from the voltage expression of the primary winding combined with the definition of coupled inductance. self and equivalent mutual inductance M z .

[0119] When the control circuit is not working, the original equivalent self-inductance value L self and the original equivalent mutual inductance value M z They are:

[0120]

[0121] When controller 1 is in effect, the first equivalent self-inductance value L self1 And the first equivalent mutual inductance value M z1 They are:

[0122]

[0123] When controller 2 is in effect, the second equivalent self-inductance value L self2 and the second equivalent mutual inductance value M z2 They are:

[0124]

[0125] The relationship between the three equivalent self-inductances is as follows: The first equivalent self-inductance value L self1 Greater than the original equivalent self-inductance value L self , original equivalent self-inductance value L self Greater than the second equivalent self-inductance value Lself2 ;

[0126] The relationship between the three equivalent mutual inductances is as follows: The first equivalent mutual inductance value M z1 Less than the original equivalent mutual inductance value M z , the original equivalent mutual inductance value M z Less than the second equivalent mutual inductance value M z2 .

[0127] It can be seen that the voltage stabilizer of the present invention can increase the equivalent self-inductance and reduce the inductor current ripple of the voltage stabilizer.

[0128] Next, the transient equivalent inductance of the regulator is derived. The transient equivalent inductance can reflect the transient response speed of the regulator. The voltage-current relationship of the N-phase coupled inductor can be expressed as follows:

[0129]

[0130] V1, V2, …, V N is the voltage of each phase inductor, I1, I2, ..., I N is the current of each phase inductor.

[0131] By adding the N-phase voltages, we can get:

[0132]

[0133] Assume the duty cycle of the N-phase regulator is:

[0134]

[0135] N-1≥K≥0 and K is an integer.

[0136] Therefore, in any period T, when time t is:

[0137]

[0138] At this time, for the N-phase regulator, the inductor voltage of the K+1 phase is V in -V o , the inductor voltage of NK-1 phase is -V o , at this time the total inductor current increases.

[0139] Similarly, when time t is:

[0140]

[0141] At this time, for the N-phase regulator, the inductor voltage of the K-phase is V in -V o , the inductor voltage of the NK phase is -V o , at this time the total inductor current decreases.

[0142] And because the total inductor current is the sum of the inductor currents of each phase, that is

[0143]

[0144] Therefore, the expression of the total inductor current during the rising and falling periods in the transient state can be obtained:

[0145]

[0146]

[0147] The transient state of the multi-phase regulator can be represented by the change in the total inductor current caused by the increase in the N-phase upper bridge arm switch duty cycle disturbance ΔD in a switching cycle T. At this time:

[0148]

[0149] And because within any cycle:

[0150]

[0151] The sum of the N-phase inductor voltage during the rising and falling periods of the inductor current is obtained as:

[0152] (V1+V2+…+V N ) up =(K+1)·(V in -V o )+(NK-1)·(-V o )

[0153] (V1+V2+…+V N ) down =K·(V in -V o )+(NK)·(-V o )

[0154] Therefore, the total inductor current expression during the transient period can be obtained:

[0155]

[0156] According to the definition of transient equivalent inductance:

[0157]

[0158] Among them, ΔD is a small disturbance of the duty cycle D, T is the time of one cycle, L otr is the transient equivalent inductance, which can represent the transient response performance of the multi-phase regulator.

[0159] Therefore, the transient equivalent inductance can be obtained as:

[0160] When the control circuit is not working, the original transient equivalent inductance L otr for:

[0161]

[0162] When controller 1 is in effect, the first transient equivalent inductance L otr1 for:

[0163]

[0164] When controller 2 is activated, the second transient equivalent inductance L otr2 for:

[0165]

[0166] The second transient equivalent inductance L otr2 Smaller than the original transient equivalent inductance L otr , the original transient equivalent inductance L otr The first transient equivalent inductance L otr1 .

[0167] It can be seen that the voltage stabilizer proposed in the present invention can control the current i x Change the transient equivalent inductance and improve the transient response speed.

[0168] Therefore, a control circuit for improving the transient performance of a multi-phase regulator is implemented as follows:

[0169] When the voltage regulator is in steady state, the AC current i c The value is less than the absolute value |1.3×i cpp / 2|, the current comparator outputs a signal to controller 1, so that i x =i c , N coupled inductors have a first equivalent self-inductance value L self1 :

[0170]

[0171] At this time, the first equivalent self-inductance value L self1 Large, achieving small inductor current ripple in each phase in steady state.

[0172] When the regulator enters transient state, the AC current i c The value is greater than the absolute value |1.3×i cpp / 2|, the current comparator outputs a signal to the adder, the adder compares the values ​​of the first current sensor and the second current sensor and then outputs a signal to the controller 2, the controller drives the H-bridge switch tube C2 and the H-bridge switch tube C3, and the AC circuit applies an AC current i to the compensation secondary windingx , let i x =i c , changes the state of the bridge so that the first equivalent self-inductance value of the N coupled inductors is L self1 And the first equivalent mutual inductance value M z1 Changes to the second equivalent self-inductance value L self1 and the second equivalent mutual inductance value M z2 , so the total equivalent transient inductance of the regulator becomes:

[0173]

[0174] The second transient equivalent inductance L otr2 Less than the first transient equivalent inductance L otr1 , the current change rate becomes larger, thus achieving a fast transient response of the regulator.

[0175] Once the transient is complete, the multiphase regulator returns to steady state. During steady state operation, the AC current i c The value is less than the absolute value |1.3×i cpp / 2|, the current comparator outputs a signal to controller 1, so that i x =i c , N coupled inductors have a first equivalent self-inductance value L self1 , in steady state, each phase keeps the current ripple small.

[0176] Example 2

[0177] like Figure 2 As shown, the control circuit of the present invention includes: a first current sensor, a second current sensor, a current comparator, an adder, a controller 1 and a controller 2, four switch tubes, and an AC circuit;

[0178] The switch tube is a field effect tube, the first end of the switch tube is the drain of the field effect tube, the second end of the switch tube is the source of the field effect tube, and the third end of the switch tube is the gate of the field effect tube;

[0179] The four switch tubes include an H-bridge switch tube C1, an H-bridge switch tube C2, an H-bridge switch tube C3, and an H-bridge switch tube C4;

[0180] The first terminal of the first current sensor and the compensation primary winding (N c ) is connected to the first end;

[0181] The second end of the first current sensor is connected to the first end of the current comparator;

[0182] The third terminal of the first current sensor is connected to the first terminal of the adder;

[0183] The second end of the current comparator is connected to the first end of the controller 1;

[0184] The third terminal of the current comparator is connected to the third terminal of the controller 2;

[0185] The third end of the H-bridge switch tube C1 at the second end of the controller 1, the third end of the H-bridge switch tube C4, and the fourth end of the AC circuit are connected;

[0186] The first end of the controller 2, the third end of the controller 1 and the third end of the adder are connected;

[0187] The second end of the controller 2 is connected to the third end of the H-bridge switch tube C2, the third end of the H-bridge switch tube C3, and the third end of the AC circuit;

[0188] The first end of the second current sensor is connected to the first end of the AC circuit, the first end of the H-bridge switch tube C1, and the first end of the H-bridge switch tube C2;

[0189] The second end of the second current sensor is connected to the second end of the adder;

[0190] The second end of the H-bridge switch tube C1 and the first end of the H-bridge switch tube C3, the compensation secondary winding (N x ) is connected to the first end;

[0191] The second end of the H-bridge switch tube C2 and the first end of the H-bridge switch tube C4, the compensation secondary winding (N x ) is connected to the second end of the

[0192] The second end of the AC circuit is connected to the second end of the H-bridge switch tube C3 and the second end of the H-bridge switch tube C4;

[0193] The first current sensor detects the current i on the bridge c ;

[0194] The second current sensor detects the compensating secondary winding (N x ) of the current i x ;

[0195] The current comparator receives the signal of the first current sensor, when the current i c The value satisfies the equation i c >|1.3×i cpp / 2|, the output signal is sent to controller 2. When the equation is not satisfied, the output signal is sent to controller 1.

[0196] The adder converts the current i c and current i xThe difference e is sent to the controller 1 and the controller 2;

[0197] The controller 1 receives the signal of the current comparator and the signal of the adder, and outputs signals to the AC circuit, the H-bridge switch tube C1 and the H-bridge switch tube C4;

[0198] The controller 2 receives the signal of the current comparator and the signal of the adder, and outputs signals to the AC circuit, the H-bridge switch tube C2 and the H-bridge switch tube C3;

[0199] The AC circuit cooperates with the four switching tubes to generate the required AC current;

[0200] Among them, |1.3×i cpp / 2| is the current i c The absolute value of the steady-state peak-to-peak value leaving a 30% margin.

[0201] Therefore, a control circuit for improving the transient performance of a multi-phase regulator is implemented as follows:

[0202] When the voltage regulator is in steady state, the AC current i c The value is less than the absolute value |1.3×i cpp / 2|, the current comparator outputs a signal to controller 1, so that i x =i c , N coupled inductors have a first equivalent self-inductance value L self1 :

[0203]

[0204] At this time, the first equivalent self-inductance value L self1 Large, achieving small current ripple in each phase in steady state.

[0205] When the regulator enters transient state, the AC current i c The value is greater than the absolute value |1.3×i cpp / 2|, the current comparator outputs a signal to the adder, the adder compares the values ​​of the first current sensor and the second current sensor and then outputs a signal to the controller 2, the controller drives the H-bridge switch tube C2 and the H-bridge switch tube C3, and the AC circuit applies an AC current i to the compensation secondary winding x , let i x =i c , changes the state of the bridge so that the first equivalent self-inductance value of the N coupled inductors is L self1 And the first equivalent mutual inductance value M z1 Changes to the second equivalent self-inductance value L self1 and the second equivalent mutual inductance value M z2 , so the total equivalent transient inductance of the regulator becomes:

[0206]

[0207] The second transient equivalent inductance L otr2 Less than the first transient equivalent inductance L otr1 , the current change rate becomes larger, thus achieving a fast transient response of the regulator.

[0208] Once the transient is complete, the multiphase regulator returns to steady state. During steady state operation, the AC current i c The value is less than the absolute value |1.3×i cpp / 2|, the current comparator outputs a signal to controller 1, so that i x =i c , N coupled inductors have a first equivalent self-inductance value L self1 , in steady state, each phase keeps the current ripple small.

[0209] Example 3

[0210] like Figure 3 As shown, the instantaneous principle diagram of the current sudden increase judgment of the control circuit of a conductive inductor multi-phase voltage regulator of the present invention, the current i c The peak-to-peak value is i cpp In order to leave a certain margin, the current i c The peak-to-peak value is i cpp A 30% margin is reserved, so the stable region of the regulator is considered to be from -1.3×i cpp / 2 to 1.3×i cpp / 2, from Figure 3 It can be seen that when the regulator operates in steady state, the current i c The current comparator outputs a signal to the controller 1 to keep the inductor current ripple of the regulator small.

[0211] When the multiphase regulator enters transient state, the output resistance R o The resistance current suddenly increases, and the current i c As a result, the current i c Reach 1.3×i cpp / 2, the voltage regulator detects the occurrence of a transient, and the current comparator outputs a signal to the controller 2. The controller 2 controls the H-bridge switch tubes C2 and C3 and the AC circuit to generate an AC current flowing through the compensation secondary winding, so that the equivalent transient inductance becomes smaller, thereby accelerating the transient response speed of the voltage regulator.

[0212] When the multiphase regulator recovers from transient state to a new steady state, the resistor current increases to a new current, i cThe current also increases to a new current, and the current comparator outputs a signal to the controller 1. The controller 1 controls the H-bridge switch tube C1 and the H-bridge switch tube C4 and the AC circuit to generate an AC current flowing through the compensation secondary winding, so that the equivalent self-inductance of each phase becomes larger, thereby reducing the inductor current ripple of the regulator.

[0213] Example 4

[0214] like Figure 4 As shown, the instantaneous principle diagram of the current sudden decrease judgment of the control circuit of a conductive inductor multi-phase voltage regulator of the present invention, the current i c The peak-to-peak value is i cpp In order to leave a certain margin, the current i c The peak-to-peak value is i cpp A 30% margin is reserved, so the stable region of the regulator is considered to be from -1.3×i cpp / 2 to 1.3×i cpp / 2, from Figure 4 It can be seen that when the regulator operates in steady state, the current i c The current comparator outputs a signal to the controller 1 to keep the inductor current ripple of the regulator small.

[0215] When the multiphase regulator enters transient state, the output resistance R o The resistance current suddenly increases, and the current i c It decreases accordingly, that is, the current i c Arrival -1.3×i cpp / 2, the voltage regulator detects the occurrence of a transient, and the current comparator outputs a signal to the controller 2. The controller 2 controls the H-bridge switch tubes C2 and C3 and the AC circuit to generate an AC current flowing through the compensation secondary winding, so that the equivalent transient inductance becomes smaller, thereby accelerating the transient response speed of the voltage regulator.

[0216] When the multiphase regulator recovers from the transient state to the new steady state, the resistor current decreases to the new current, i c The current is also reduced to a new current, and the current comparator outputs a signal to the controller 1. The controller 1 controls the H-bridge switch tube C1 and the H-bridge switch tube C4 and the AC circuit to generate an AC current flowing through the compensation secondary winding, so that the equivalent self-inductance of each phase becomes larger, thereby reducing the inductor current ripple of the regulator.

[0217] From the above analysis, it can be seen that the secondary windings of N coupled inductors and the primary winding of the compensation inductor are connected in series to build a bridge. The secondary winding of the compensation inductor generates an induced voltage in its primary winding, which affects the state of the bridge and further changes the equivalent self-inductance and equivalent mutual inductance of the N coupled inductors, thereby reducing the current ripple of the regulator and improving the transient response speed of the regulator.

[0218] In the description of the present invention, it should be noted that the terms "center", "upper", "lower", "left", "right", "vertical", "horizontal", "inner", "outer", etc., indicating the orientation or positional relationship, are based on the orientation or positional relationship shown in the drawings, and are only for the convenience of describing the present invention and simplifying the description, rather than indicating or implying that the elements or modules referred to must have a specific orientation, be constructed and operated in a specific orientation, and therefore cannot be understood as limiting the present invention. In addition, the terms "first", "second", and "third" are used for descriptive purposes only, and cannot be understood as implying or indicating relative importance.

[0219] Unless otherwise clearly specified and limited, the terms "connection" and "installation" should be understood in a broad sense, for example, it can be a fixed connection, a detachable connection, or an integral connection; it can be a mechanical connection or an electrical connection; it can be a direct connection or a link through an intermediate medium, or it can be the internal communication of two components. For ordinary technicians in this field, the specific meanings of the above terms in the present invention can be understood according to specific circumstances.

[0220] As described above, the above embodiments are only used to illustrate the technical solutions of the present application, rather than to limit them. The description of the embodiments disclosed in the present invention enables professional and technical personnel in the field to use or implement the present invention. They can still modify the technical solutions recorded in the aforementioned embodiments, or make equivalent replacements for some of the technical features therein. However, these replacements or modifications do not deviate the essence of the corresponding technical solutions from the spirit and scope of the technical solutions of the embodiments of the present application.

Claims

1. A control circuit of a conductive inductor multiphase regulator, characterized in that: include: A first current sensor, a second current sensor, a current comparator, an adder, a controller 1, a controller 2, four switch tubes, and an AC circuit; The switch tube is a field effect tube, the first end of the switch tube is the drain of the field effect tube, the second end of the switch tube is the source of the field effect tube, and the third end of the switch tube is the gate of the field effect tube; The four switch tubes include an H-bridge switch tube C1, an H-bridge switch tube C2, an H-bridge switch tube C3, and an H-bridge switch tube C4; The first terminal of the first current sensor and the compensation primary winding (N c ) is connected to the first end; The second end of the first current sensor is connected to the first end of the current comparator; The third terminal of the first current sensor is connected to the first terminal of the adder; The second end of the current comparator is connected to the first end of the controller 1; The third terminal of the current comparator is connected to the third terminal of the controller 2; The third end of the H-bridge switch tube C1 at the second end of the controller 1, the third end of the H-bridge switch tube C4, and the fourth end of the AC circuit are connected; The first end of the controller 2, the third end of the controller 1 and the third end of the adder are connected; The second end of the controller 2 is connected to the third end of the H-bridge switch tube C2, the third end of the H-bridge switch tube C3, and the third end of the AC circuit; The first end of the second current sensor is connected to the first end of the AC circuit, the first end of the H-bridge switch tube C1, and the first end of the H-bridge switch tube C2; The second end of the second current sensor is connected to the second end of the adder; The second end of the H-bridge switch tube C1 and the first end of the H-bridge switch tube C3, the compensation secondary winding (N x ) is connected to the first end; The second end of the H-bridge switch tube C2 and the first end of the H-bridge switch tube C4, the compensation secondary winding (N x ) is connected to the second end of the The second end of the AC circuit is connected to the second end of the H-bridge switch tube C3 and the second end of the H-bridge switch tube C4; The first current sensor detects the current i on the bridge c ; The second current sensor detects the compensating secondary winding (N x ) of the current i x ; The current comparator receives the signal of the first current sensor, when the current i c The value satisfies the equation i c >|1.3×i cpp / 2|, the output signal is sent to controller 2. When the equation is not satisfied, the output signal is sent to controller 1. The adder converts the current i c and current i x The difference e is sent to the controller 1 and the controller 2; The controller 1 receives the signal of the current comparator and the signal of the adder, and outputs signals to the AC circuit, the H-bridge switch tube C1 and the H-bridge switch tube C4; The controller 2 receives the signal of the current comparator and the signal of the adder, and outputs signals to the AC circuit, the H-bridge switch tube C2 and the H-bridge switch tube C3; The AC circuit cooperates with the four switching tubes to generate the required AC current; Among them, |1.3×i cpp / 2| is the current i c The absolute value of the steady-state peak-to-peak value leaving a 30% margin.

2. The control circuit of a conductive inductor multi-phase regulator according to claim 1, characterized in that: After a transient occurs in the conductive inductor multiphase regulator, the i in the current comparator cpp The value of i is the new steady state cpp value.

3. A conductive inductor multi-phase regulator according to the control circuit of a conductive inductor multi-phase regulator as claimed in claim 1, characterized in that: include: Input power (V in )、2N switch tubes (S1~S N , Q1~Q N ), N coupled inductors, compensation inductors, output capacitors (C o )、output resistance (R o ); The 2N switch tubes include N upper bridge arm switch tubes (S1-S N ) and N lower bridge arm switch tubes (Q1~Q N ); The N coupled inductors include N primary windings (N a1 ~N aN ) and N secondary windings (N b1 ~N bN ); The compensating inductor comprises a compensating primary winding (N c ) and the compensating secondary winding (N x ); The input power supply (V in ) and the positive electrode of the N upper bridge arm switch tubes (S1~S N ) is connected to the first end; The input power supply (V in ) and the negative electrode of the N lower bridge arm switch tubes (Q1~Q N ) of the second terminal, the output capacitor (C o ) of the second end, the output resistance (R o ) is connected to the second end of the The N primary windings (N a1 ~N aN )'s ith primary winding (N ai ) and the N upper bridge arm switch tubes (S1~S N ) of the i-th upper bridge arm switch tube (S i ) of the second end, the N lower bridge arm switch tubes (Q1~Q N )’s ith lower bridge arm switch tube (Q i ) is connected to the first end; The N primary windings (N a1 ~N aN ) and the output resistor (R o ) first end, output capacitor (C o ) is connected to the first end; The N secondary windings (N b1 ~N bN ) and the compensating primary winding (N c ) are connected in series; Wherein, i=1, 2, 3...N, N≥2 and is an integer.

4. A conductive inductor multi-phase regulator according to claim 3, characterized in that: The N primary windings (N a1 ~N aN )'s ith primary winding (N ai ) and the N secondary windings (N b1 ~N bN )'s ith secondary winding (N bi ) have the same name as each other; Compensation primary winding (N c ) and the first end of the compensating secondary winding (N x ) have the same name as each other; Wherein, i=1, 2, 3...N, N≥2 and is an integer.

5. The conductive inductor multi-phase regulator according to claim 3, characterized in that: The N coupled inductors have a first equivalent self-inductance value L self1 And the first equivalent mutual inductance value M z1 , The N coupled inductors have a second equivalent self-inductance value L self2 and the second equivalent mutual inductance value M z2 , The second equivalent self-inductance value is smaller than the first equivalent self-inductance value, and the second equivalent mutual inductance value is larger than the first equivalent mutual inductance value; Where, N ≥ 2 and is an integer, La is the primary winding inductance, Lb is the secondary winding inductance, Lc is the compensated primary winding inductance, M is the mutual inductance between the primary winding and the secondary winding, M x To compensate the mutual inductance of the primary winding and the secondary winding.

6. The conductive inductor multi-phase regulator according to claim 3, characterized in that: The coupling coefficient of each of the N coupled inductors is equal, and the N primary windings (N a1 ~N aN ) each primary winding has the same number of turns, and the N secondary windings (N b1 ~N bN ) each secondary winding has the same number of turns.

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