Method for generating output voltage using HSC converter

Abstract

An HSC voltage conversion module includes: an input voltage; a transformer without a primary winding but comprising a secondary winding magnetically coupled by a magnetic core; a first switching bridge and a second switching bridge connected to the transformer and an input voltage; and an output capacitor connected to a single node of the transformer and providing an output voltage that is a quarter of the input voltage.

Description

[0001] CROSS-REFERENCE TO RELATED APPLICATIONS

[0002] This application claims priority to U.S. Patent Application No. 63 / 524,316, filed on June 30, 2023. The entire contents of that application are incorporated herein by reference. Technical Field

[0003] The present invention relates to DC-DC converters. More particularly, the present invention relates to a hybrid switched capacitor (HSC) converter providing an output voltage that is one quarter of the input voltage. Background Art

[0004] It is known to use two-stage conversion, where the first stage is an LLC resonant converter and the second stage is a point-of-load (POL) converter. The LLC resonant converter is used as an intermediate bus converter in which there is zero voltage switching (ZVS) on the primary side or high voltage (HV) side and zero current switching (ZCS) on the secondary side or low voltage (LV) side. If isolation is not required, the first stage can be a switched capacitor converter with non-regulated zero voltage switching.

[0005] In order to reduce the footprint of the converter, high switching frequency operation is required in the first and second stages. However, high frequency operation, especially operation on the first stage (i.e., 1MHz to 2MHz), results in higher losses (i.e., switching, gate drive, and conduction losses). In some applications, a higher step-down ratio of the first stage may be desired to reduce losses (including, for example, switching and conduction losses). For 48V power delivery applications, the step-down ratio of the first stage is 8:1 to provide a 6V intermediate bus. Reducing the 48V input voltage to a 6V intermediate bus voltage can achieve higher power density while maintaining high efficiency. Switched capacitor (SC) converters provide high conversion rates, but SC converters are complex and bulky in terms of floating driver requirements and the number of switches and ceramic capacitors required. LLC converters with center-tapped rectifiers provide high conversion rates with lower complexity, but when isolation is not required, non-isolated topologies are preferred due to increased power density. In low output voltage applications, LLC converters with center-tapped rectifiers can be used, but this topology has suboptimal copper utilization because the secondary winding is turned on for half of the switching cycle.

[0006] It is known to use a hybrid switched capacitor (HSC) converter, which overcomes the limitations of switched capacitor converters and LLC converters in terms of high step-down ratios. The HSC converter combines the advantages of a switched capacitor converter with the high step-down ratio capability of a transformer-based converter. By transferring energy through capacitors and magnetic devices, efficiency and power density can be significantly improved. However, the known HSC converters cannot provide an output voltage that is one-quarter of the input voltage. In applications where the output voltage is one-quarter of the input voltage, a different topology is required, such as the LLC topology. In an LLC converter, since the current in the secondary winding is half-wave rectified, the current peaks are large, resulting in losses. Summary of the invention

[0007] In order to overcome the above-mentioned problems, an exemplary embodiment of the present invention provides an HSC converter which includes a transformer without a primary winding and provides an output voltage which is one quarter of an input voltage.

[0008] According to an example embodiment, an HSC voltage conversion module includes: an input voltage; a transformer having no primary winding but including a secondary winding magnetically coupled through a magnetic core; a first switching bridge and a second switching bridge connected to the transformer and the input voltage; and an output capacitor connected to a single node of the transformer and providing an output voltage that is one quarter of the input voltage.

[0009] The HSC voltage conversion module may also include a first resonant circuit connected between the first switch bridge and the transformer and a second resonant circuit connected between the second switch bridge and the transformer. The first resonant circuit may include a first resonant capacitor, the second resonant circuit may include a second resonant capacitor, and the first resonant circuit and the second resonant circuit may rely on the leakage inductance of the transformer.

[0010] Each of the first switch bridge and the second switch bridge may include a first switch, a second switch, and a third switch connected in series. The secondary winding of the transformer may include a first winding and a second winding. The HSC voltage conversion module may be bidirectional.

[0011] According to an exemplary embodiment of the present invention, a converter includes: an input terminal receiving an input voltage; a first switch bridge connected in parallel across the input voltage and including a first switch, a second switch, and a third switch connected in series, a first node between the first switch and the second switch, and a third node between the second switch and the third switch; a second switch bridge including a fourth switch, a fifth switch, and a sixth switch connected in series, a second node between the fourth switch and the fifth switch, and a fourth node between the fifth switch and the sixth switch; an output capacitor; a transformer including a single winding including a first secondary winding and a second secondary winding, the first secondary winding and the second secondary winding being physically connected to each other to define a secondary winding set and being magnetically coupled through a magnetic core, and the transformer including: a single tap connected to the output capacitor; a first resonant circuit connected between the first node and a first end of the single winding; a second resonant circuit connected between the second node and a second end of the single winding, the second end being opposite to the first end of the single winding; and an output terminal connected to the first output capacitor to provide a first output voltage, the first output voltage being one-fourth of the input voltage.

[0012] The first resonant circuit may include a first resonant capacitor, the second resonant circuit may include a second resonant capacitor, and the first resonant circuit and the second resonant circuit may depend on a leakage inductance of a transformer.

[0013] The converter may be bi-directional such that power may flow from the input terminals to the output terminals and from the output terminals to the input terminals.

[0014] The above and other features, components, characteristics, steps and advantages of the present invention will become more apparent from the following detailed description of exemplary embodiments of the present invention with reference to the accompanying drawings. BRIEF DESCRIPTION OF THE DRAWINGS

[0015] Figure 1 A related art hybrid switched capacitor (HSC) converter is shown.

[0016] Figure 2 An HSC converter without a primary winding but with two connected secondary windings is shown.

[0017] Figure 3 Shows Figure 2 Different current paths for the HSC converter.

[0018] Figure 4A and Figure 4B Shows Figure 2 Figure 2. Plot of different waveforms of an HSC converter.

[0019] Figure 5A table comparing the properties of LLC and HSC converters is shown.

[0020] Figure 6 Graph showing different waveforms for an LLC converter.

[0021] Figure 7 Graph showing different waveforms for an HSC converter.

[0022] Figure 8 Shows Figure 6 and Figure 7 Table of different properties of LLC converter and HSC converter used in.

[0023] 9A to 9C Shows the display Figure 2 A graph of the waveform of the simulation results of the HSC converter. DETAILED DESCRIPTION

[0024] Figure 1 is a circuit diagram of a related art hybrid switched capacitor (HSC) converter including a single output. Figure 1 The HSC converter includes an input voltage Vin, a first bridge and a second bridge, a transformer connected between the first bridge and the second bridge, a first resonant circuit connected between the first bridge and the transformer, a second resonant circuit connected between the second bridge and the transformer, a first output capacitor Cout connected to the transformer, and an output terminal Vout connected to the output capacitor Cout.

[0025] Figure 1 The input voltage Vin of the HSC converter may be any suitable DC voltage source, and may provide any suitable DC voltage, including, for example, 48 V. The output voltage Vout depends on the number of turns in the windings L11 to L22, as given by the following equation (1).

[0026] Figure 1The first bridge and the second bridge of the HSC converter may be connected in parallel between the input voltage Vin and the ground. The first bridge includes switches Q1, Q2, Q3, wherein the second switch Q2 is connected in series between the first switch Q1 and the third switch Q3, and the second bridge includes switches Q4, Q5, Q6, wherein the fifth switch Q5 is connected in series between the fourth switch Q4 and the sixth switch Q6. The first node may be located between the first switch Q1 and the second switch Q2, the second node may be located between the second switch Q2 and the third switch Q3, the third node may be located between the fourth switch Q4 and the fifth switch Q5, and the fourth node may be located between the fifth switch Q5 and the sixth switch Q6. The switches Q1 to Q6 may be divided into a first switch group including switches Q1, Q3, Q5 and a second switch group including Q2, Q4, Q6. The first switch group and the second switch group may be complementarily controlled using a 180° phase-shifted pulse width modulator (PWM). The first switch group and the second switch group can be controlled with the same fixed duty cycle (which can be close to 50%) to reduce or minimize the root mean square (RMS) current. The switches Q1 to Q6 can be controlled by a controller that provides drive signals to the switches Q1 to Q6. Any suitable controller can be used and can be implemented in hardware and / or software. The controller can be configured and / or programmed to provide the functionality described herein.

[0027] Figure 1 The transformer of the HSC converter may be a multi-tap autotransformer including a single winding, the single winding including a first winding L12, a second winding L22, a third winding L21, and a fourth winding L11. The first winding L12 is physically connected to the second winding L22, the second winding L22 is physically connected to the third winding L21, and the third winding L21 is physically connected to the fourth winding L11. The first end of the single winding of the transformer (i.e., the end of the first winding L12 not connected to the second winding L22) may be connected to the first resonant circuit, and the second end of the single winding of the transformer (i.e., the end of the fourth winding L11 not connected to the third winding L21) may be connected to the second resonant circuit. The first winding L12, the second winding L22, the third winding L21, and the fourth winding L11 may be magnetically coupled by a magnetic core.

[0028] Figure 1 A single winding of the transformer of the HSC converter may include a first tap between the first winding L12 and the second winding L22, a second tap between the second winding L22 and the third winding L21, and a third tap between the third winding L21 and the fourth winding L11. The first tap may be connected to a fourth node between the fifth switch Q5 and the sixth switch Q6. The second tap may be connected to the output capacitor Cout. The third tap may be connected to a second node between the second switch Q2 and the third switch Q3.

[0029] exist Figure 1 In the HSC converter, the first winding group or primary winding group of the transformer may include: a winding between the first end of the transformer and the first tap of the transformer (i.e., the first winding L12) and a winding between the second end of the transformer and the third tap of the transformer (i.e., the fourth winding L11). The second winding group or secondary winding group of the transformer may include a winding between the first tap and the second tap of the transformer (i.e., the second winding L22) and a winding between the second tap and the third tap of the transformer (i.e., the third winding L21). Since the windings L11 to L22 are physically connected to each other, the primary winding group and the secondary winding group are not isolated from each other. Figure 1 The HSC converter is a non-isolated DC-DC converter.

[0030] exist Figure 1 In the HSC converter of FIG. 1 , the first resonant circuit may include a first resonant capacitor Cres1 , and the first resonant circuit may be connected between the first winding L12 and a first node between the first switch Q1 and the second switch Q2 . Figure 1 In the HSC converter of the present invention, the second resonant circuit may include a second resonant capacitor Cres2, and the second resonant circuit may be connected between the fourth winding L11 and a third node located between the fourth switch Q4 and the fifth switch Q5. The first resonant circuit and the second resonant circuit may use the leakage inductance of the transformer. Alternatively, the first resonant circuit and the second resonant circuit may use discrete inductors.

[0031] Figure 1 The output terminal Vout of the HSC converter provides a single output voltage. The single output voltage may be a non-regulated output voltage. The ratio between the input voltage Vin and the output voltage Vout is given by the following equation:

[0032]

[0033] Wherein, Vout is the output voltage of the output terminal Vout, Vin is the voltage of the input voltage Vin, N1 is the number of turns of the first winding L12 and the fourth winding L11, and N2 is the number of turns of the second winding L22 and the third winding L21. The output voltage Vou can be adjusted by adjusting the number of turns in the windings L11 to L22. However, no matter how the number of turns in the windings L11 to L22 is adjusted, the output voltage Vout cannot be adjusted to a quarter of the input voltage.

[0034] In applications where the output voltage is one quarter of the input voltage, a different topology is usually required, such as the LLC topology. In an LLC converter, since the current in the secondary winding is half-wave rectified, the current peaks are large, resulting in losses.

[0035] Figure 2 An HSC converter is shown in which the output voltage is one quarter of the input voltage. Figure 2 In the HSC converter, the autotransformer includes a first winding L22 and a second winding L21, but does not include any primary winding. Figure 2 The autotransformer consists of a single tap connected to the output capacitor Cout. Figure 1 Compared with the HSC converter, Figure 2 The HSC converter does not include the first winding L12 or the fourth winding L11. Figure 2 The transformer in includes only two windings (ie, windings L22, L21). Figure 2 The transformer in the embodiment includes only a secondary winding and does not include any primary winding. By not including the primary winding, the copper loss generated in the primary winding, i.e., the loss caused by the current flowing through the copper foil, is eliminated. Since the structure of the transformer is simplified, the space occupied by the primary winding can be used more efficiently.

[0036] and Figure 1 The HSC converter is similar to Figure 2 The HSC converter includes an input voltage Vin, a first bridge and a second bridge, a transformer connected between the first bridge and the second bridge, a first resonant circuit connected between the first bridge and the transformer, a second resonant circuit connected between the second bridge and the transformer, a first output capacitor Cout connected to the transformer, and an output terminal Vout connected to the output capacitor Cout.

[0037] Figure 2The first bridge and the second bridge of the HSC converter may be connected in parallel between the input voltage Vin and the ground. The first bridge includes switches Q1, Q2, Q3, wherein the second switch Q2 is connected in series between the first switch Q1 and the third switch Q3, and the second bridge includes switches Q4, Q5, Q6, wherein the fifth switch Q5 is connected in series between the fourth switch Q4 and the sixth switch Q6. The first node may be located between the first switch Q1 and the second switch Q2, the second node may be located between the second switch Q2 and the third switch Q3, the third node may be located between the fourth switch Q4 and the fifth switch Q5, and the fourth node may be located between the fifth switch Q5 and the sixth switch Q6. The switches Q1 to Q6 may be divided into a first switch group including switches Q1, Q3, Q5 and a second switch group including Q2, Q4, Q6. The first switch group and the second switch group may be complementarily controlled using a 180° phase-shifted pulse width modulator (PWM). The first switch group and the second switch group can be controlled with the same fixed duty cycle (which can be close to 50%) to reduce or minimize the root mean square (RMS) current. The switches Q1 to Q6 can be controlled by a controller that provides drive signals to the switches Q1 to Q6. Any suitable controller can be used and can be implemented in hardware and / or software. The controller can be configured and / or programmed to provide the functionality described herein.

[0038] Figure 2 The transformer of the HSC converter may be a single-tap autotransformer including a single winding including a first winding L22 and a second winding L21. The first winding L22 is physically connected to the second winding L21. The first end of the single winding of the transformer (i.e., the end of the first winding L22 not connected to the second winding L21) may be connected to the first resonant circuit, and the second end of the single winding of the transformer (i.e., the end of the second winding L21 not connected to the first winding L22) may be connected to the second resonant circuit. The first winding L22 and the second winding L21 may be magnetically coupled by a magnetic core.

[0039] Figure 2 A single winding of the transformer of the HSC converter may include a single tap between the first winding L22 and the second winding L21. The single tap may be connected to the output capacitor Cout.

[0040] Figure 2 The transformer of the HSC converter includes a single winding set or secondary winding set. The single winding set or secondary winding set of the transformer may include a winding between a first end of the transformer and a second end of the transformer (i.e., a first winding L22 and a second winding L21). Since the windings L21 and L22 are physically connected to each other, Figure 2 The HSC converter is a non-isolated DC-DC converter.

[0041] exist Figure 2 In the HSC converter of FIG. 1 , the first resonant circuit may include a first resonant capacitor Cres1 , and the first resonant circuit may be connected between the first winding L12 and a first node between the first switch Q1 and the second switch Q2 . Figure 2 In the HSC converter of the present invention, the second resonant circuit may include a second resonant capacitor Cres2, and the second resonant circuit may be connected between the fourth winding L11 and a third node located between the fourth switch Q4 and the fifth switch Q5. The first resonant circuit and the second resonant circuit may use the leakage inductance of the transformer. Alternatively, the first resonant circuit and the second resonant circuit may use discrete inductors.

[0042] Figure 1 The output terminal Vout of the HSC converter provides a single output voltage. The single output voltage may be a non-regulated output voltage. The ratio between the input voltage Vin and the output voltage Vout is given by the following equation:

[0043]

[0044] Figure 3 Shows Figure 2Different current paths in the HSC converter of FIG. The first current path starts from one terminal of the input voltage Vin, the turned-on switch Q1 and the first node, passes through the first resonant circuit and the fourth node, passes through the first winding L22 (i.e., winding 1) and a single tap, passes through the output capacitor Cout, and then reaches the other terminal of the input voltage Vin connected to the ground, thereby generating a first current loop, which includes the input voltage, the first switch Q1, the first resonant circuit, the first winding L22 (i.e., winding 1) and the output capacitor Cout. The second current path starts from the second node, passes through the second resonant circuit, passes through the turned-on fifth switch and the fourth node, passes through the first winding L21 (i.e., winding 1) and a single tap, passes through the output capacitor Cout, then passes through the third switch Q3 and returns to the second node, thereby generating a second current loop, which includes the second resonant circuit, the fifth switch Q5, the first winding L22 (i.e., winding 1), the output capacitor Cout and the third switch Q3. The first current path and the second current path in the first winding L22 (i.e., winding 1) induce a third current path in the second winding L21 (i.e., winding 2). The third current path passes through the second winding L21 (i.e., winding 2) and a single tap, passes through the output capacitor Cout, then passes through the third switch Q3 and returns to the second winding L21 (i.e., winding 2), thereby generating a third current loop, which includes the second winding L21 (i.e., winding 2), the output capacitor Cout and the third switch Q3. The output terminal Vout is connected to the output capacitor Cout and the first current loop, the second current loop and the third current loop. In Figure 3 In the embodiment, the capacitance of the first resonant capacitor Cres1 and the second resonant capacitor Cres2 are the same, so that Cres1=Cres2=Cres. In addition, the first switch group (including switches Q1, Q3, Q5) is turned on, and the second switch group (including switches Q2, Q4, Q6) is turned off. Switches Q1 to Q6 can be switched at a certain frequency according to the following equation:

[0045]

[0046] Among them, f sw is the switching frequency, L k is the leakage inductance of the winding, C cres is the capacitance of the resonant capacitors Cres1, Cres2. The voltage of the resonant capacitors Cres1, Cres2 is half of the input voltage, as given by the following equation:

[0047]

[0048] Among them, V cres is the voltage of the resonant capacitors Cres1 and Cres2, and V inis the voltage of the input voltage. The currents in the first resonant circuit and the second resonant circuit are equal and are given by the following equation:

[0049]

[0050] Among them, I cres1 ,I cres2 is the current in the first resonant circuit and the second resonant circuit, I cres is the current passing through the first resonant circuit or the second resonant circuit, and I outDC is the output current. The root mean square (RMS) current through switch Q1 is half the current through the first resonant circuit, as given by the following equation:

[0051]

[0052] Among them, I Q1(rms) is the RMS current through the first switch Q1. The RMC current through the third switch Q3 is 1.5 times the current through the second resonant circuit, as given by the following equation:

[0053]

[0054] Among them, I Q3(rms) is the RMS current through the first switch Q3. Figure 3 The second winding L21 (marked as winding 1 in Figure 3 The current marked as winding 2 in FIG. 1 is the current through the first resonant circuit and the second resonant circuit, as given by the following equation:

[0055]

[0056] Among them, I winding1 is the current through the first winding L22, and I winding2 is the current passing through the second winding L21.

[0057] Figure 4A and Figure 4B Shows Figure 2The simulated waveforms of a 1500W HSC converter include a 54V input, a 13.5V output (= Vin / 4 = 54V / 4) and an output current of 111A. The switches in the first bridge and the second bridge can be driven by two PWM signals with arbitrary frequencies but with a phase difference of 180°. Therefore, a resonant current Ires can be generated in the first resonant circuit and the second resonant circuit, each resonant circuit including a resonant capacitor and a resonant inductor, which is the leakage inductance or discrete inductor of the transformer. The resonant current Ires flows through each of the switches Q1 and Q2. Twice the resonant current Ires is induced in the second winding L21 of the transformer, and three times the resonant current Ires (which is a combination of the currents in the second current loop and the third current loop) flows through the switch Q3. As Figure 4A As shown, twice the resonant current Ires flows through the first winding L22 (ie, winding 1) and the second winding L21 (ie, winding 2) as currents Is1 and Is2, respectively. Figure 4B It is shown that the output voltage is one quarter of the input voltage (i.e., Vout=Vin / 4). The RMS current Iq1 through the first switch Q1 is approximately 22.26A, the RMS current Iq2 through the second switch Q2 is approximately 21.78A, and the RMC current Iq3 through the third switch Q3 is approximately 66.57A. The RMS current Is1 through the first winding L22 (winding 1) is approximately 62.29A, and the average current Is1 through the first winding L22 (winding 1) is approximately 55.65A. The RMS current IS2 through the second winding L21 (winding 2) is approximately 62.16A, and the average current Is1 through the first winding L22 (winding 1) is approximately 55.50A. The RMS voltage of the output voltage is approximately 13.15V, and the peak-to-peak voltage of the output voltage is approximately 115.74mV.

[0058] Compared with the LLC converter, the transformer winding current is Figure 2 The HSC converter of the embodiment of the present invention is full-wave rectified, thereby improving the current utilization of a single winding and reducing winding losses (including, for example, losses caused by the winding being included in a printed circuit board (PCB)). Since the current flowing in the output-side switch (i.e., Figure 2 The effective current flowing in the switches Q3 and Q6 in the output side can be reduced, thereby also reducing the loss generated in the output side switch.

[0059] Figure 5 shows a comparison between LLC converter and Figure 2The LLC converter and the HSC converter are compared in a table, where both the LLC converter and the HSC converter provide an output voltage that is one-fourth of the input voltage. As shown in the table, the LLC converter has a turns ratio of 4:1:1, while the HSC converter has a turns ratio of 1:1. Both the LLC converter and the HSC converter include four 80V transistors in the primary circuit and two 40V transistors in the secondary circuit. The current in the primary winding of the LLC converter is given by the following equation:

[0060]

[0061] The HSC converter has no primary winding. The half-wave current in the secondary winding of the LLC converter is given by the following equation:

[0062]

[0063] The full wave current in the secondary winding of the HSC converter is half of that of the LLC converter and is given by the following equation:

[0064]

[0065] The RMS current in the first and second secondary windings of the LLC converter is given by the following equations:

[0066]

[0067] The RMS current in the first and second secondary windings of the HSC converter is about 29% of that of the LLC converter and is given by the following equation:

[0068]

[0069] The RMS current in the primary switch in both LLC and HSC converters is half-wave and is given by:

[0070]

[0071] The RMS current in the secondary switch of the LLC converter is half-wave rectified and is given by the following equation:

[0072]

[0073] The RMS current in the secondary switch of the HSC converter is half-wave rectified and is three-quarters of that of the LLC converter and is given by the following equation:

[0074]

[0075] Figure 6 and Figure 7A graph showing the current waveforms of an HSC converter providing an output voltage that is one-quarter of the input voltage and a comparative LLC converter. Both the LLC converter and the HSC converter are capable of providing 1500W of power. The input voltage is 54V, the output voltage is 13.5V, and the output current is 111A. For the LLC converter, Figure 6 In the upper part, a graph of the current waveforms of the switches Q1 to Q3 is shown, and in the lower part, a graph of the current waveforms of the primary winding and the first and second secondary windings is shown. For the HSC converter, Figure 7 In the upper part, graphs of current waveforms of the switches Q1 to Q3 are shown, and in the lower part, graphs of current waveforms of the first secondary winding and the second secondary winding are shown. Figure 8 The table in Figure 6 and Figure 7 . In the LLC converter, through the first switch Q1, the peak current is 43.5A and the RMS current is 21.8A; through the second switch Q2, the peak current is 43.5A and the RMS current is 21.8A; and through the third switch Q3, the peak current is 174A and the RMS current is 87.2A. Through the primary winding, the peak current is 43.5A and the RMS current is 30.8A; through the first secondary winding, the peak current is 174A and the RMS current is 87.2A; and through the second secondary winding, the peak current is 174A and the RMS current is 87.2A. In the HSC converter, through the first switch Q1, the peak current is 43.5A and the RMS current is 21.8A; through the second switch Q2, the peak current is 43.5A and the RMS current is 21.8A; and through the third switch Q3, the peak current is 131A and the RMS current is 65.4A. There is no primary winding in the HSC converter. Through the first secondary winding, the peak current is 87.2A and the RMS current is 61.6A; and through the second secondary winding, the peak current is 87.2A and the RMS current is 61.6A.

[0076] 9A to 9C shows that when power flows from the output terminal Vout to the input voltage Vin Figure 2 Waveforms of a simulation of the bidirectional behavior of the HSC converter. 9A to 9C The waveforms of a simulation of a 1080W HSC converter are shown, which includes a 13.5V input at the output terminal Vout, a 54V output at the input voltage Vin (=Vin*4=13.5V*4), and a 20A output current. Figure 4A and 4B Normal operation is similar to that shown, 9A to 9C It is demonstrated that power can flow in opposite directions, wherein the switches are driven by two PWM signals so that the resonant current Ires flows in the first resonant circuit and the second resonant circuit. Fig. 9C It is confirmed that the output voltage (ie, the voltage at the input voltage Vin) is four times the input voltage (ie, the voltage at the output terminal Vout) (Vin=4×Vout). The peak-to-peak output voltage is about 230.42mV. The RMS input voltage is 13.5V, and the RMS output voltage is about 52.93V.

[0077] According to the simulation results discussed above, it has been confirmed that an output voltage that is one-fourth of the input voltage can be provided with the primary winding removed, the effective current flowing in the secondary winding is reduced by 29% compared to the comparative LLC converter system, and the effective current flowing through the secondary switch is reduced by 25% compared to the LLC converter system, and Figure 1 The HSC converter can be operated bidirectionally and can be used as a bidirectional power supply.

[0078] It should be understood that the above description is only used to describe the present invention. Without departing from the present invention, those skilled in the art can design various substitutions and modifications. Therefore, the present invention is intended to include all these substitutions, modifications and variations that fall within the scope of the appended claims.

Claims

1. A HSC voltage conversion module, comprising: Input voltage; a transformer having no primary winding but including secondary windings magnetically coupled via a magnetic core; a first switching bridge and a second switching bridge connected to the transformer and the input voltage; as well as An output capacitor is connected to a single node of the transformer and provides an output voltage that is one-fourth of the input voltage.

2. The HSC voltage conversion module according to claim 1, further comprising: a first resonant circuit connected between the first switching bridge and the transformer; as well as The second resonant circuit is connected between the second switch bridge and the transformer.

3. The HSC voltage conversion module according to claim 2, wherein: The first resonant circuit includes a first resonant capacitor; The second resonant circuit includes a second resonant capacitor; and The first resonant circuit and the second resonant circuit are dependent on a leakage inductance of the transformer.

4. The HSC voltage conversion module according to any one of claims 1 to 3, wherein: Each of the first switching bridge and the second switching bridge includes a first switch, a second switch, and a third switch connected in series.

5. The HSC voltage conversion module according to any one of claims 1 to 3, wherein: The secondary winding of the transformer includes a first winding and a second winding.

6. The HSC voltage conversion module according to any one of claims 1 to 3, wherein: The HSC voltage conversion module is bidirectional.

7. A converter comprising: An input terminal for receiving an input voltage; A first switching bridge connected in parallel across the input voltage and comprising: A first switch, a second switch, and a third switch connected in series; a first node between the first switch and the second switch; and a third node, between the second switch and the third switch; The second switch bridge comprises: a fourth switch, a fifth switch and a sixth switch connected in series; a second node between the fourth switch and the fifth switch; and a fourth node, between the fifth switch and the sixth switch; Output capacitor; Transformer, including: a single winding including a first secondary winding and a second secondary winding physically connected to each other to define a secondary winding set and magnetically coupled by a magnetic core; and a single tap connected to the output capacitor; a first resonant circuit connected between the first node and a first end of the single winding; a second resonant circuit connected between the second node and a second end of the single winding, the second end being opposite to the first end of the single winding; and An output terminal is connected to a first output capacitor to provide a first output voltage, wherein the first output voltage is one quarter of the input voltage.

8. The converter according to claim 7, wherein: The first resonant circuit includes a first resonant capacitor; The second resonant circuit includes a second resonant capacitor; and The first resonant circuit and the second resonant circuit are dependent on a leakage inductance of the transformer.

9. The converter according to claim 7 or 8, wherein: The converter is bidirectional, enabling power to flow from the input terminals to the output terminals and from the output terminals to the input terminals.

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