Methods, apparatus, equipment, media and products for determining crystal oscillator frequency offset

Abstract

This application provides a method, apparatus, device, medium, and product for determining crystal oscillator frequency offset. The method includes: performing mixing processing on a low local oscillator carrier to generate a corresponding first mixing result; the low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal; the theoretical signal is a downlink signal received without Doppler frequency offset; performing mixing processing on a high local oscillator carrier to generate a corresponding second mixing result; the high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal; and determining the crystal oscillator frequency offset based on the first mixing result and the second mixing result. The crystal oscillator frequency offset determination method of this application determines the crystal oscillator frequency offset by generating a first mixing result after mixing processing the low local oscillator carrier and a second mixing result after mixing processing the high local oscillator carrier, utilizing the characteristics of the low and high local oscillator carriers. This provides a way to determine the crystal oscillator frequency offset without relying on other data such as satellite ephemeris.

Description

Technical Field

[0001] This application relates to the field of wireless communication technology, and in particular to a method, apparatus, device, medium and product for determining crystal oscillator frequency offset. Background Technology

[0002] In high-speed relative motion, especially in cellular network high-speed rail scenarios and low-orbit satellite communication scenarios, frequency synchronization between communication devices needs to take into account the large Doppler frequency offset introduced by high-speed motion and the crystal oscillator frequency offset introduced by the crystal oscillator accuracy of the communication devices.

[0003] As crystal oscillators age and their accuracy decreases, or the frequency accuracy of the crystal itself is limited, and because the terminal has difficulty determining the crystal oscillator frequency offset, the uplink signal sent by the terminal still has a large range of frequency offset when it reaches the base station, causing the uplink random access performance to deteriorate or even become unaccessible.

[0004] Therefore, there is currently a problem where the uplink signal has a large range of frequency offset due to the difficulty in determining the crystal oscillator frequency offset. Summary of the Invention

[0005] This application provides a method, apparatus, device, medium, and product for determining crystal oscillator frequency offset, in order to solve the problem that the uplink signal has a large range of frequency offset due to the difficulty in determining the crystal oscillator frequency offset.

[0006] The first aspect of this application provides a method for determining the frequency offset of a crystal oscillator, comprising:

[0007] The low local oscillator carrier is mixed to generate a corresponding first mixing result; the low local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal; the theoretical signal is the downlink signal received when no Doppler frequency offset occurs;

[0008] The high-frequency local oscillator carrier is mixed to generate a corresponding second mixing result; the high-frequency local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal;

[0009] The crystal oscillator frequency offset is determined based on the first mixing result and the second mixing result.

[0010] Further, in the method described above, the mixing process of the low local oscillator carrier to generate the corresponding first mixing result includes:

[0011] The low local oscillator carrier and the first actual signal are mixed and processed to generate a first in-phase quadrature IQ complex signal; the first actual signal is the first downlink signal received when Doppler frequency offset occurs.

[0012] The first IQ complex signal and the preset intermediate frequency signal are subjected to digital mixing and digital down-conversion processing to generate the corresponding first mixing result.

[0013] Further, in the method described above, the step of mixing the low local oscillator carrier and the first actual signal and generating a complex signal to generate a first in-phase quadrature IQ complex signal includes:

[0014] The low local oscillator carrier and the first actual signal are subjected to analog mixing to generate the first intermediate signal;

[0015] The first intermediate signal is low-pass filtered to generate the second intermediate signal;

[0016] An analog-to-digital converter is used to sample and process the second intermediate signal to generate the first IQ complex signal.

[0017] Further, in the method described above, the step of performing digital mixing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to generate a corresponding first mixing result includes:

[0018] The first IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding third intermediate signal;

[0019] The third intermediate signal is subjected to negative frequency filtering and downsampling to generate the corresponding first mixing result.

[0020] Further, in the method described above, the mixing process of the high local oscillator carrier to generate the corresponding second mixing result includes:

[0021] The high-frequency carrier and the second actual signal are mixed and processed to generate a second IQ complex signal; the second actual signal is the second downlink signal received when Doppler frequency offset occurs.

[0022] The second IQ complex signal and the preset intermediate frequency signal are subjected to digital mixing and digital down-conversion processing to generate the corresponding second mixing result.

[0023] Further, in the method described above, the step of mixing the high local oscillator carrier and the second actual signal and generating a complex signal to generate a second IQ complex signal includes:

[0024] The high local oscillator carrier and the second actual signal are subjected to analog mixing to generate a fourth intermediate signal;

[0025] The fourth intermediate signal is low-pass filtered to generate the fifth intermediate signal;

[0026] The fifth intermediate signal is sampled and processed using an analog-to-digital converter to generate the second IQ complex signal.

[0027] Further, in the method described above, the step of performing digital mixing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding second mixing result includes:

[0028] The second IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding sixth intermediate signal;

[0029] The sixth intermediate signal is subjected to negative frequency filtering and downsampling to generate the corresponding second mixing result.

[0030] Furthermore, in the method described above, the first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal during reception.

[0031] Further, in the method described above, determining the crystal oscillator frequency offset based on the first mixing result and the second mixing result includes:

[0032] The first mixing result, the second mixing result, and the preset intermediate frequency are input into the preset crystal oscillator frequency offset calculation algorithm, and the crystal oscillator frequency offset is determined by the preset crystal oscillator frequency offset calculation algorithm; the preset intermediate frequency is the frequency of the preset intermediate frequency signal.

[0033] Furthermore, in the method described above, the method further includes:

[0034] The first mixing result, the second mixing result, the theoretical signal frequency, and the preset intermediate frequency are input into the preset Doppler frequency offset algorithm, and the Doppler frequency offset is determined by the preset Doppler frequency offset algorithm; the theoretical signal frequency is the frequency of the theoretical signal.

[0035] The first mixing result, the second mixing result, the low local oscillator carrier frequency, and the preset intermediate frequency are input into the preset crystal oscillator uncertainty algorithm, and the crystal oscillator uncertainty is determined by the preset crystal oscillator uncertainty algorithm; the low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

[0036] Furthermore, in the method described above, after inputting the first mixing result, the second mixing result, the low local oscillator carrier frequency, and the preset intermediate frequency into a preset crystal oscillator uncertainty algorithm to determine the crystal oscillator uncertainty, the method further includes:

[0037] The crystal oscillator uncertainty, Doppler frequency offset, and theoretical signal frequency are input into a preset compensation algorithm, and the preset compensation algorithm is used to generate the uplink compensation frequency.

[0038] Frequency compensation is performed on the uplink signal based on the uplink compensation frequency.

[0039] A second aspect of this application provides a crystal oscillator frequency offset determination device, comprising:

[0040] The first mixing module is used to perform mixing processing on the low local oscillator carrier to generate a corresponding first mixing result; the low local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal; the theoretical signal is the downlink signal received when no Doppler frequency offset occurs;

[0041] The second mixing module is used to perform mixing processing on the high local oscillator carrier to generate a corresponding second mixing result; the high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal;

[0042] The determining module is used to determine the crystal oscillator frequency offset based on the first mixing result and the second mixing result.

[0043] Furthermore, in the apparatus described above, the first mixer module is specifically used for:

[0044] The low local oscillator carrier and the first actual signal are mixed and processed to generate a first in-phase quadrature IQ complex signal; the first actual signal is the first downlink signal received when Doppler frequency offset occurs; the first IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally downconverted to generate a corresponding first mixing result.

[0045] Furthermore, in the apparatus described above, when the first mixing module performs mixing and complex signal generation processing on the low local oscillator carrier and the first actual signal to generate the first in-phase quadrature IQ complex signal, it is specifically used for:

[0046] The low local oscillator carrier and the first actual signal are subjected to analog mixing to generate a first intermediate signal; the first intermediate signal is subjected to low-pass filtering to generate a second intermediate signal; the second intermediate signal is sampled by an analog-to-digital converter to generate a first IQ complex signal.

[0047] Furthermore, in the apparatus described above, when the first mixing module performs digital mixing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to generate the corresponding first mixing result, it is specifically used for:

[0048] The first IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate a corresponding third intermediate signal; the third intermediate signal is then subjected to negative frequency filtering and downsampling to generate a corresponding first mixing result.

[0049] Furthermore, in the apparatus described above, the second mixer module is specifically used for:

[0050] The high local oscillator carrier and the second actual signal are mixed and processed to generate a second IQ complex signal; the second actual signal is the second downlink signal received when Doppler frequency offset occurs; the second IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally downconverted to generate a corresponding second mixing result.

[0051] Furthermore, in the apparatus described above, when the second mixing module performs mixing and complex signal generation processing on the high local oscillator carrier and the second actual signal to generate the second IQ complex signal, it is specifically used for:

[0052] The high local oscillator carrier and the second actual signal are subjected to analog mixing to generate the fourth intermediate signal; the fourth intermediate signal is subjected to low-pass filtering to generate the fifth intermediate signal; the fifth intermediate signal is sampled by an analog-to-digital converter to generate the second IQ complex signal.

[0053] Furthermore, in the apparatus described above, when the second mixing module performs digital mixing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to generate the corresponding second mixing result, it is specifically used for:

[0054] The second IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding sixth intermediate signal; the sixth intermediate signal is subjected to negative frequency filtering and downsampling to generate the corresponding second mixing result.

[0055] Furthermore, in the device described above, the first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal during reception.

[0056] Furthermore, in the apparatus described above, the determining module is specifically used for:

[0057] The first mixing result, the second mixing result, and the preset intermediate frequency are input into the preset crystal oscillator frequency offset calculation algorithm, and the crystal oscillator frequency offset is determined by the preset crystal oscillator frequency offset calculation algorithm; the preset intermediate frequency is the frequency of the preset intermediate frequency signal.

[0058] Furthermore, the apparatus as described above further includes:

[0059] The frequency offset determination module is used to input the first mixing result, the second mixing result, the theoretical signal frequency, and the preset intermediate frequency into a preset Doppler frequency offset algorithm, and use the preset Doppler frequency offset algorithm to determine the Doppler frequency offset; the theoretical signal frequency is the frequency of the theoretical signal;

[0060] The uncertainty determination module is used to input the first mixing result, the second mixing result, the low local oscillator carrier frequency, and the preset intermediate frequency into the preset crystal oscillator uncertainty algorithm, and use the preset crystal oscillator uncertainty algorithm to determine the crystal oscillator uncertainty; the low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

[0061] Furthermore, the apparatus as described above further includes:

[0062] The compensation module is used to input the crystal oscillator uncertainty, Doppler frequency offset, and theoretical signal frequency into a preset compensation algorithm, and use the preset compensation algorithm to generate an uplink compensation frequency; and to perform frequency compensation on the uplink signal based on the uplink compensation frequency.

[0063] A third aspect of this application provides a communication device, comprising: a memory and a processor;

[0064] The memory stores computer-executed instructions;

[0065] The processor executes computer execution instructions stored in the memory to implement the crystal oscillator frequency offset determination method as described in any of the first aspects.

[0066] A fourth aspect of this application provides a computer-readable storage medium storing computer-executable instructions, which, when executed by a processor, are used to implement the crystal oscillator frequency offset determination method according to any one of the first aspects.

[0067] The fifth aspect of this application provides a computer program product, including a computer program that, when executed by a processor, implements the crystal oscillator frequency offset determination method according to any one of the first aspects.

[0068] This application provides a method, apparatus, device, medium, and product for determining crystal oscillator frequency offset. The method includes: performing mixing processing on a low local oscillator carrier to generate a corresponding first mixing result; the low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal; the theoretical signal is a downlink signal received without Doppler frequency offset; performing mixing processing on a high local oscillator carrier to generate a corresponding second mixing result; the high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal; and determining the crystal oscillator frequency offset based on the first mixing result and the second mixing result. The crystal oscillator frequency offset determination method of this application determines the crystal oscillator frequency offset by generating a first mixing result after mixing processing the low local oscillator carrier and a second mixing result after mixing processing the high local oscillator carrier, utilizing the characteristics of the low and high local oscillator carriers. This provides a way to determine the crystal oscillator frequency offset without relying on other data such as satellite data, thus reducing the frequency offset of the uplink signal. Attached Figure Description

[0069] The accompanying drawings, which are incorporated in and form part of this specification, illustrate embodiments consistent with this application and, together with the description, serve to explain the principles of this application.

[0070] Figure 1 A schematic diagram of the device structure for the crystal oscillator frequency offset determination method provided in this application;

[0071] Figure 2 Flowchart of the crystal oscillator frequency offset determination method provided in this application Figure 1 ;

[0072] Figure 3 Flowchart of the crystal oscillator frequency offset determination method provided in this application Figure 2 ;

[0073] Figure 4a A mixing diagram illustrating the crystal oscillator frequency offset determination method provided in this application. Figure 1 ;

[0074] Figure 4b A mixing diagram illustrating the crystal oscillator frequency offset determination method provided in this application. Figure 2 ;

[0075] Figure 4c A mixing diagram illustrating the crystal oscillator frequency offset determination method provided in this application. Figure 3 ;

[0076] Figure 5 A schematic diagram of the crystal oscillator frequency offset determination device provided in this application;

[0077] Figure 6 A schematic diagram of the communication device provided in this application.

[0078] The accompanying drawings illustrate specific embodiments of this application, which will be described in more detail below. These drawings and descriptions are not intended to limit the scope of the concept in any way, but rather to illustrate the concept of this application to those skilled in the art through reference to particular embodiments. Detailed Implementation

[0079] Exemplary embodiments will now be described in detail, examples of which are illustrated in the accompanying drawings. When the following description relates to the drawings, unless otherwise indicated, the same numbers in different drawings denote the same or similar elements. The embodiments described in the following exemplary embodiments do not represent all embodiments consistent with this application. Rather, they are merely examples of apparatuses and methods consistent with some aspects of this application as detailed in the appended claims.

[0080] The technical solutions of this application will be described in detail below with reference to specific embodiments. These specific embodiments can be combined with each other, and the same or similar concepts or processes may not be described again in some embodiments. The embodiments of this application will be described below with reference to the accompanying drawings.

[0081] To clearly understand the technical solution of this application, the conceptual process of the technical solution will first be described in detail. The high-speed relative motion of communication transceivers introduces a large Doppler frequency offset, which poses a significant challenge to frequency synchronization, especially in cellular network scenarios on high-speed rail and low-Earth orbit satellite communication scenarios. Both the terminal on the high-speed rail and the base station on the satellite will experience large Doppler frequency offsets due to high-speed motion. In the initial access phase, after the terminal completes initial downlink time-frequency synchronization based on the downlink broadcast signal, it needs to estimate the pre-compensation value of the uplink transmission frequency based on downlink measurements or other auxiliary means. This ensures that when the compensated uplink random access signal reaches the base station, the signal frequency is within the frequency range allowed by the base station, thereby guaranteeing the success rate of uplink random access and reducing the user's network access waiting time.

[0082] Since the terminal cannot distinguish the frequency components from the downlink frequency offset estimation results, it is difficult to determine the crystal oscillator frequency offset. This will result in a large range of frequency offset when the pre-compensated uplink signal reaches the base station, causing uplink random access performance to deteriorate or even become unaccessible.

[0083] Therefore, there is currently a problem where the uplink signal has a large range of frequency offset due to the difficulty in determining the crystal oscillator frequency offset.

[0084] Therefore, addressing the problem of large-scale uplink signal frequency offset caused by the difficulty in determining crystal oscillator frequency offset in existing technologies, the inventors discovered in their research that the crystal oscillator frequency offset can be determined by the characteristics of the low and high local oscillator carriers. By mixing the target signal to the required low-intermediate frequency and then extracting the signal through low-pass filtering, two reception results are obtained for the same signal or two signals with similar timings: a first mixing result and a second mixing result. The crystal oscillator frequency offset is then determined based on the first and second mixing results.

[0085] Specifically, the process for determining the crystal oscillator frequency offset is as follows:

[0086] The low local oscillator carrier is mixed to generate a corresponding first mixing result. The low local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal. The theoretical signal is the downlink signal received without Doppler frequency offset. The high local oscillator carrier is mixed to generate a corresponding second mixing result. The high local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal. The crystal oscillator frequency offset is determined based on the first and second mixing results.

[0087] The crystal oscillator frequency offset determination method of this application generates a first mixing result by mixing the low local oscillator carrier and a second mixing result by mixing the high local oscillator carrier, and determines the crystal oscillator frequency offset by utilizing the characteristics of the low and high local oscillator carriers. This provides a way to determine the crystal oscillator frequency offset without relying on other data such as satellite navigation or satellite ephemeris, and without requiring multiple interactions with the base station.

[0088] Based on the above-mentioned inventive discovery, the inventor has proposed the technical solution of this application.

[0089] The application scenarios of the crystal oscillator frequency offset determination method provided in the embodiments of this application are described below. For example... Figure 1 As shown in the figure, a partial structure of the communication device 10 is illustrated. The communication device 10 includes an antenna 11, an RF chip 12, and a baseband chip 13. The RF chip 12 includes multiple devices not shown in the figure, such as a bandpass filter, a low-pass filter, a low-noise amplifier, and an analog-to-digital converter. The baseband chip 13 includes multiple devices not shown in the figure, such as a frequency synchronization module and digital down-conversion related devices.

[0090] For example, when the communication device 10 receives a downlink signal, it receives it through the antenna 11. At this time, the downlink signal is processed by the radio frequency chip 12 and then transmitted to the baseband 13. In order to accurately pre-compensate the uplink signal, the communication device 10 performs the following crystal oscillator frequency offset determination process:

[0091] ① After preprocessing the downlink signal, such as bandpass filtering and low-noise amplification, the downlink signal is frequency-divided by a local crystal oscillator to generate a low local oscillator carrier and a high local oscillator carrier. At this time, the frequency division is based on the theoretical signal and the preset intermediate frequency signal. The theoretical signal is the downlink signal received without Doppler frequency offset, and the preset intermediate frequency signal is the intermediate frequency that can be configured when performing quadrature demodulation under the low intermediate frequency structure.

[0092] ② Perform mixing processing on the low local oscillator carrier to generate the corresponding first mixing result.

[0093] ③ Perform mixing processing on the high local oscillator carrier to generate the corresponding second mixing result.

[0094] ④ Determine the crystal oscillator frequency offset based on the first mixing result and the second mixing result.

[0095] After determining the crystal oscillator frequency offset, the crystal oscillator uncertainty and Doppler frequency offset can be further determined in a manner similar to step ④ of this embodiment.

[0096] The embodiments of this application are described below with reference to the accompanying drawings.

[0097] Figure 2 Flowchart of the crystal oscillator frequency offset determination method provided in this application Figure 1,like Figure 2 As shown, the execution subject of this application embodiment is a crystal oscillator frequency offset determination device. This crystal oscillator frequency offset determination device can be integrated into a communication device, such as a terminal device. The crystal oscillator frequency offset determination method provided in this embodiment includes the following steps:

[0098] Step S101: Perform mixing processing on the low local oscillator carrier to generate the corresponding first mixing result. The low local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal. The theoretical signal is the downlink signal received when no Doppler frequency offset occurs.

[0099] In this embodiment, when a communication device, such as a terminal, receives a downlink signal, it receives the downlink signal transmission at a known frequency. If the Doppler frequency offset is not considered, the downlink signal corresponding to this known frequency can be considered to have no Doppler frequency offset. In this case, the corresponding downlink signal is the aforementioned theoretical signal. However, in actual transmission, the downlink signal will introduce a Doppler frequency offset, and the actual signal frequency is the sum of the known frequency and the Doppler frequency offset.

[0100] For example, suppose the downlink signal sent from the base station to the terminal is at frequency f c During wireless transmission, a Doppler frequency offset f is introduced due to the relative motion between the base station and the terminal. d Therefore, the carrier frequency at which the downlink signal reaches the terminal antenna becomes f. ue =f c +f d The theoretical signal is then the frequency f. c .

[0101] In this embodiment, the preset intermediate frequency (IF) signal can be an IF frequency that is allowed to be configured when performing quadrature demodulation under a low IF structure. The low local oscillator carrier can be obtained by dividing the theoretical signal and the preset IF signal using a local crystal oscillator. For example, if the theoretical signal is frequency f... c The preset intermediate frequency signal is f IF The theoretical low local oscillator carrier is Low local oscillator carrier is The theoretical low local oscillator carrier is In generation frequency Due to the uncertainty of the crystal oscillator (ppm, a unit of crystal oscillator precision, one part per million), the low local oscillator carrier... in, This is the offset frequency of the crystal oscillator with a low local oscillator.

[0102] Optionally, in this embodiment, the mixing process for the low local oscillator carrier may include processing steps such as mixing, filtering, and noise reduction. Mixing can be performed multiple times; for example, an initial mixing can be performed based on the frequency of the actual signal, followed by subsequent digital mixing to obtain the final first mixing result.

[0103] Step S102: Perform mixing processing on the high local oscillator carrier to generate the corresponding second mixing result. The high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal.

[0104] In this embodiment, the high local oscillator carrier is similar to the low local oscillator carrier. The high local oscillator carrier can be obtained by frequency division of the theoretical signal and the preset intermediate frequency signal by the local crystal oscillator.

[0105] For example, if the theoretical signal has a frequency f c The preset intermediate frequency signal is f IF The theoretical high local oscillator carrier is High local oscillator carrier is The theoretical high local oscillator carrier is In generation frequency Due to the uncertainty of the crystal oscillator (xppm, a unit of crystal oscillator precision, one part per million), the high local oscillator carrier... in, To adjust the frequency of the crystal oscillator to a high local oscillator, let but It can be represented as:

[0106]

[0107] Optionally, in this embodiment, the mixing process for the high local oscillator carrier may include processing steps such as mixing, filtering, and noise reduction. Mixing can be performed multiple times; for example, an initial mixing can be performed based on the frequency of the actual signal, followed by subsequent digital mixing to obtain the final second mixing result.

[0108] Step S103: Determine the crystal oscillator frequency offset based on the first mixing result and the second mixing result.

[0109] In this embodiment, since the first mixing result is related to the low local oscillator carrier and the second mixing result is related to the high local oscillator carrier, and given the theoretical signal and the preset intermediate frequency signal, the crystal oscillator frequency offset can be determined based on the first mixing result and the second mixing result using a preset crystal oscillator frequency offset calculation algorithm.

[0110] This application provides a method for determining crystal oscillator frequency offset. The method includes: performing mixing processing on a low local oscillator carrier to generate a corresponding first mixing result. The low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal. The theoretical signal is the downlink signal received when no Doppler frequency offset occurs. Performing mixing processing on a high local oscillator carrier to generate a corresponding second mixing result. The high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal. The crystal oscillator frequency offset is determined based on the first mixing result and the second mixing result.

[0111] The crystal oscillator frequency offset determination method of this application generates a first mixing result by mixing the low local oscillator carrier and a second mixing result by mixing the high local oscillator carrier, and determines the crystal oscillator frequency offset by utilizing the characteristics of the low and high local oscillator carriers. This provides a way to determine the crystal oscillator frequency offset without relying on other data such as satellite data.

[0112] Figure 3 Flowchart of the crystal oscillator frequency offset determination method provided in this application Figure 2 ,like Figure 3 As shown, the crystal oscillator frequency offset determination method provided in this embodiment is a further refinement based on the crystal oscillator frequency offset determination method provided in the previous embodiment of this application. The crystal oscillator frequency offset determination method provided in this embodiment includes the following steps.

[0113] Step S201 involves mixing the low local oscillator carrier and the first actual signal, and generating a complex signal to produce a first in-phase quadrature IQ complex signal. The first actual signal is the first downlink signal received when Doppler frequency offset occurs.

[0114] In this embodiment, the frequency of the first actual signal is the sum of the frequency of the theoretical signal and the Doppler frequency offset, i.e., f in the previous embodiment. ue By mixing the low local oscillator carrier and the first actual signal and generating complex signals, the in-phase quadrature IQ complex signals needed for subsequent use can be obtained, providing a basis for determining the crystal oscillator frequency offset. Here, I represents in-phase and Q represents quadrature.

[0115] Optionally, in this embodiment, S201 may include the following process:

[0116] The low local oscillator carrier and the first actual signal are subjected to analog mixing to generate the first intermediate signal.

[0117] The first intermediate signal is low-pass filtered to generate the second intermediate signal.

[0118] An analog-to-digital converter is used to sample and process the second intermediate signal to generate the first IQ complex signal.

[0119] In this embodiment, analog mixing refers to mixing in the analog domain, which can be implemented using an RF chip. After analog mixing, high-frequency and low-frequency components are obtained; that is, the first intermediate signal contains both high-frequency and low-frequency components. At this point, a low-pass filter is used to perform low-pass filtering on the first intermediate signal, retaining the low-frequency components; thus, the second intermediate signal is the signal corresponding to the low-frequency components. Simultaneously, an analog-to-digital converter is used to sample the second intermediate signal to generate a first IQ complex signal, which can be further processed by the baseband.

[0120] For example, in this embodiment, the frequency of the theoretical signal is as follows: Figure 4a As shown, the slashed filled box represents the negative frequency. When performing analog mixing, the first intermediate signal is generated as follows: Figure 4b As shown in the figure, LPF stands for Low Pass Filter. The dashed box represents the low pass filter filtering the first intermediate signal to retain the low frequency components.

[0121] Step S202: Perform digital mixing and digital downconversion processing on the first IQ complex signal and the preset intermediate frequency signal to generate the corresponding first mixing result.

[0122] In this embodiment, digital mixing processing refers to digital mixing performed in the digital domain. The baseband can perform digital mixing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to obtain a signal that meets the baseband synchronization requirements and the first mixing result.

[0123] Optionally, in this embodiment, S202 may include the following process:

[0124] The first IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding third intermediate signal.

[0125] The third intermediate signal is subjected to negative frequency filtering and downsampling to generate the corresponding first mixing result.

[0126] In this embodiment, the preset intermediate frequency signal used in the digital mixing process can be a negative frequency. For example, the negative frequency f mix =-f IF The digital signal required by the baseband, namely the third intermediate signal, can be obtained through this digital mixing.

[0127] Simultaneously, after negative frequency filtering and downsampling, the digital baseband signal with the required rate for the frequency synchronization module in the baseband can be obtained. At this point, the first mixing result, also known as the total frequency offset Δf1 of the first mixing, is:

[0128]

[0129] Among them, f ue The carrier frequency of the first actual signal. f is the frequency of the low local oscillator carrier. mix For the aforementioned negative frequency, f c f is the frequency of the theoretical signal. d For Doppler frequency shift, f IF This is the preset intermediate frequency signal.

[0130] Step S203 involves mixing the high local oscillator carrier and the second actual signal, and generating a complex signal to produce a second IQ complex signal. The second actual signal is the second downlink signal received when Doppler frequency offset occurs.

[0131] In this embodiment, the frequency of the second actual signal is the sum of the frequency of the theoretical signal and the Doppler frequency offset, or f from the previous embodiment. ue This indicates that the second actual signal can be the same as or different from the first actual signal. By mixing the high local oscillator carrier and the second actual signal and generating complex signals, the in-phase quadrature IQ complex signal needed for subsequent use can be obtained, providing a basis for determining the crystal oscillator frequency offset.

[0132] Optionally, the first actual signal and the second actual signal are the same, or there is a preset time difference between the first actual signal and the second actual signal during reception. The preset time difference can be set according to the accuracy requirements of the crystal oscillator frequency offset in actual applications. If the highest accuracy is required, the preset time difference can be set to zero, that is, the first actual signal and the second actual signal are the same. When the first actual signal and the second actual signal are the same, their Doppler frequency offsets are the same. However, when there is a preset time difference between the first actual signal and the second actual signal during reception, their Doppler frequency offsets are different, but the difference between them is small.

[0133] Optionally, in this embodiment, S203 may include the following process:

[0134] The high local oscillator carrier and the second actual signal are subjected to analog mixing to generate a fourth intermediate signal.

[0135] The fourth intermediate signal is low-pass filtered to generate the fifth intermediate signal.

[0136] The fifth intermediate signal is sampled and processed using an analog-to-digital converter to generate the second IQ complex signal.

[0137] In this embodiment, similar to the process of low local oscillator carrier mixing, analog mixing can be implemented using an RF chip. After analog mixing, high-frequency and low-frequency components are obtained, meaning the fourth intermediate signal contains both. At this point, the fourth intermediate signal is low-pass filtered to retain the low-frequency components, resulting in the fifth intermediate signal being the signal corresponding to the low-frequency components. Simultaneously, an analog-to-digital converter is used to sample the fifth intermediate signal to generate a second IQ complex signal, which can be further processed by the baseband.

[0138] For example, in this embodiment, the frequency of the theoretical signal is as follows: Figure 4a As shown, the slashed filled box represents the negative frequency. When performing analog mixing, a fourth intermediate signal is generated as follows: Figure 4cAs shown in the figure, LPF is a low-pass filter, and the dashed box represents the low-pass filter filtering the fourth intermediate signal to retain the low-frequency components.

[0139] Step S204: Perform digital mixing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to generate the corresponding second mixing result.

[0140] In this embodiment, the baseband can perform digital mixing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to obtain a signal that meets the baseband synchronization requirements and the second mixing result.

[0141] Optionally, in this embodiment, S204 may include the following process:

[0142] The second IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding sixth intermediate signal.

[0143] The sixth intermediate signal is subjected to negative frequency filtering and downsampling to generate the corresponding second mixing result.

[0144] In this embodiment, the preset intermediate frequency signal used in the digital mixing process can be a negative frequency. For example, the negative frequency f mix =-f IF The digital signal required by the baseband, namely the sixth intermediate signal, can be obtained through this digital mixing.

[0145] Simultaneously, after negative frequency filtering and downsampling, the digital baseband signal with the required rate for the frequency synchronization module in the baseband can be obtained. At this point, the total frequency offset Δf2 of the second mixing result, also known as the second mixing result, is:

[0146]

[0147] Among them, f ue The frequency of the second actual signal, f is the frequency of the high local oscillator carrier. mix For the aforementioned negative frequency, f c f is the frequency of the theoretical signal. d For Doppler frequency shift, f IF The preset intermediate frequency signal is ε, which is the signal from the previous embodiment. The ratio of .

[0148] Step S205: Input the first mixing result, the second mixing result, and the preset intermediate frequency into the preset crystal oscillator frequency offset calculation algorithm, and use the preset crystal oscillator frequency offset calculation algorithm to determine the crystal oscillator frequency offset. The preset intermediate frequency is the frequency of the preset intermediate frequency signal.

[0149] In this embodiment, the preset crystal oscillator frequency offset calculation algorithm can be as follows:

[0150]

[0151] in, For low local oscillator frequency offset of crystal oscillator, Let x be the theoretical low local oscillator carrier wave, and let x be the uncertainty of the crystal oscillator. To achieve the high local oscillator frequency offset of the crystal oscillator, It is a theoretical high local oscillator carrier.

[0152] Optionally, in this embodiment, the Doppler frequency offset and crystal oscillator uncertainty can also be determined, as follows:

[0153] The first mixing result, the second mixing result, the theoretical signal frequency, and the preset intermediate frequency are input into the preset Doppler frequency offset algorithm, and the Doppler frequency offset is determined using the preset Doppler frequency offset algorithm. The theoretical signal frequency is the frequency of the theoretical signal.

[0154] The first mixing result, the second mixing result, the low local oscillator carrier frequency, and the preset intermediate frequency are input into the preset crystal oscillator uncertainty algorithm, and the crystal oscillator uncertainty is determined using the preset crystal oscillator uncertainty algorithm. The low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

[0155] In this embodiment, the preset Doppler frequency offset algorithm can be as follows:

[0156]

[0157] The algorithm for pre-setting crystal oscillator uncertainty can be as follows:

[0158]

[0159] or

[0160]

[0161] Optionally, in this embodiment, after determining the crystal oscillator uncertainty, the uplink signal can be further compensated, as follows:

[0162] The crystal oscillator uncertainty, Doppler frequency offset, and theoretical signal frequency are input into the preset compensation algorithm, and the preset compensation algorithm is used to generate the uplink compensation frequency.

[0163] Frequency compensation is performed on the uplink generated signal based on the uplink compensation frequency.

[0164] In this embodiment, the preset compensation algorithm can be as follows:

[0165]

[0166] in, To compensate for the frequency, f tThe uplink signal frequency. For the uplink crystal oscillator frequency offset, This is the upward Doppler frequency offset.

[0167] After frequency compensation of the uplink signal using the aforementioned uplink compensation frequency, the frequency at which the uplink signal reaches the transmission target can be made close to the expected transmission frequency f. t .

[0168] Optionally, if the baseband mixer module of the communication device can support a sampling rate... High enough to satisfy the Nyquist sampling theorem, that is:

[0169]

[0170] Among them, w s To determine the uplink signal bandwidth, uplink frequency pre-compensation can be implemented at the digital mixer in the baseband. The pre-compensated baseband signal is then used at the carrier frequency f. t Send. Based on this compensation method, if the downlink frequency offset is accurately estimated, both the uplink crystal oscillator frequency offset and the uplink Doppler frequency offset can be accurately compensated.

[0171] Optionally, if the baseband sampling rate cannot meet the requirements of digital mixing, then uplink frequency pre-compensation needs to be implemented at the intermediate frequency analog mixer. In this case, the signal uses the pre-compensated carrier frequency f. tx send:

[0172]

[0173] Based on this compensation method, due to the corrected carrier frequency f tx The corresponding crystal oscillator frequency deviation will become f tx ×10 -6 ×x, therefore, after the uplink signal reaches the base station side with the introduction of uplink crystal oscillator frequency offset and uplink Doppler frequency offset, it is related to the desired frequency f. t There is a very small deviation Δf between them. t :

[0174]

[0175] But generally Δf t Typically only at the Hz level, its impact on uplink open-loop frequency synchronization is negligible.

[0176] The crystal oscillator frequency offset determination method in this embodiment first receives a carrier frequency of f via an antenna. cThe real signal is then mixed to the required low-IF frequency using both high and low local oscillator methods through a low-IF structure RF front-end. This signal is then extracted via low-pass filtering, resulting in two different reception results for the same signal. Since the mixing result is obtained by performing two analog mixing operations on the same signal or two signals of similar frequency at close intervals, the Doppler frequency offset carried by these two signals remains unchanged or almost unchanged. The two high and low local oscillator carriers obtained by the terminal through crystal oscillator frequency division carry two observations regarding the uncertainty of the crystal oscillator. Therefore, the crystal oscillator frequency offset can be calculated based on these two downlink frequency offset measurements.

[0177] The crystal oscillator frequency offset determination method in this embodiment enables communication devices, such as terminals, to estimate the downlink crystal oscillator frequency offset and uplink frequency pre-compensation value without relying on GNSS (Global Navigation Satellite System), satellite ephemeris, or multiple interactions with the base station. This allows for accurate compensation of the uplink transmission frequency, improved performance of uplink open-loop frequency synchronization, and guaranteed success rate of initial uplink random access.

[0178] Figure 5 This is a schematic diagram of the crystal oscillator frequency offset determination device provided in this application, as shown below. Figure 5 As shown, in this embodiment, the crystal oscillator frequency offset determination device 300 can be installed in a communication device. The crystal oscillator frequency offset determination device 300 includes:

[0179] The first mixing module 301 is used to perform mixing processing on the low local oscillator carrier to generate a corresponding first mixing result. The low local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal. The theoretical signal is the downlink signal received when no Doppler frequency offset occurs.

[0180] The second mixing module 302 is used to perform mixing processing on the high local oscillator carrier to generate a corresponding second mixing result. The high local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal.

[0181] The determination module 303 is used to determine the crystal oscillator frequency offset based on the first mixing result and the second mixing result.

[0182] The crystal frequency offset determination device provided in this embodiment can perform... Figure 2 The technical solution of the method embodiment shown has the same implementation principle and technical effect as... Figure 2 The methods and embodiments shown are similar and will not be described in detail here.

[0183] The crystal oscillator frequency offset determination device provided in this application is a further refinement of the crystal oscillator frequency offset determination device provided in the previous embodiment. The crystal oscillator frequency offset determination device 300 includes:

[0184] Optionally, in this embodiment, the first mixing module 301 is specifically used for:

[0185] The low local oscillator carrier and the first actual signal are mixed and processed to generate a first in-phase quadrature IQ complex signal. The first actual signal is the first downlink signal received when Doppler frequency offset occurs. The first IQ complex signal and a preset intermediate frequency signal are digitally mixed and digitally downconverted to generate the corresponding first mixing result.

[0186] Optionally, in this embodiment, when the first mixing module 301 performs mixing and complex signal generation processing on the low local oscillator carrier and the first actual signal to generate the first in-phase quadrature IQ complex signal, it is specifically used for:

[0187] The low-frequency local oscillator carrier and the first actual signal are subjected to analog mixing to generate a first intermediate signal. A low-pass filter is then applied to the first intermediate signal to generate a second intermediate signal. An analog-to-digital converter is used to sample the second intermediate signal to generate a first IQ complex signal.

[0188] Optionally, in this embodiment, when the first mixing module 301 performs digital mixing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to generate the corresponding first mixing result, it is specifically used for:

[0189] The first IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding third intermediate signal. The third intermediate signal is then subjected to negative frequency filtering and downsampling to generate the corresponding first mixing result.

[0190] Optionally, in this embodiment, the second mixing module 302 is specifically used for:

[0191] The high-frequency local oscillator carrier and the second actual signal are mixed and processed to generate a second IQ complex signal. The second actual signal is the second downlink signal received when Doppler frequency offset occurs. The second IQ complex signal and a preset intermediate frequency signal are digitally mixed and digitally downconverted to generate the corresponding second mixing result.

[0192] Optionally, in this embodiment, when the second mixing module 302 performs mixing and complex signal generation processing on the high local oscillator carrier and the second actual signal to generate the second IQ complex signal, it is specifically used for:

[0193] The high-frequency local oscillator carrier and the second actual signal are subjected to analog mixing to generate a fourth intermediate signal. A low-pass filter is then applied to the fourth intermediate signal to generate a fifth intermediate signal. An analog-to-digital converter is used to sample the fifth intermediate signal to generate a second IQ complex signal.

[0194] Optionally, in this embodiment, when the second mixing module 302 performs digital mixing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to generate the corresponding second mixing result, it is specifically used for:

[0195] The second IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding sixth intermediate signal. The sixth intermediate signal is then subjected to negative frequency filtering and downsampling to generate the corresponding second mixing result.

[0196] Optionally, in this embodiment, the first actual signal and the second actual signal are the same, or there is a preset time difference between the first actual signal and the second actual signal during reception.

[0197] Optionally, in this embodiment, the determining module 303 is specifically used for:

[0198] The first mixing result, the second mixing result, and the preset intermediate frequency are input into the preset crystal oscillator frequency offset calculation algorithm, which is used to determine the crystal oscillator frequency offset. The preset intermediate frequency is the frequency of the preset intermediate frequency signal.

[0199] Optionally, in this embodiment, the crystal oscillator frequency offset determination device 300 further includes:

[0200] The frequency offset determination module is used to input the first mixing result, the second mixing result, the theoretical signal frequency, and the preset intermediate frequency into the preset Doppler frequency offset algorithm, and to determine the Doppler frequency offset using the preset Doppler frequency offset algorithm. The theoretical signal frequency is the frequency of the theoretical signal.

[0201] The uncertainty determination module is used to input the first mixing result, the second mixing result, the low local oscillator carrier frequency, and the preset intermediate frequency into the preset crystal oscillator uncertainty algorithm, and to determine the crystal oscillator uncertainty using the preset crystal oscillator uncertainty algorithm. The low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

[0202] Optionally, in this embodiment, the crystal oscillator frequency offset determination device 300 further includes:

[0203] The compensation module is used to input the crystal oscillator uncertainty, Doppler frequency offset, and theoretical signal frequency into a preset compensation algorithm, and then use the preset compensation algorithm to generate an uplink compensation frequency. Frequency compensation is then performed on the uplink signal based on the uplink compensation frequency.

[0204] The crystal frequency offset determination device provided in this embodiment can perform... Figure 2 The technical solution of the method embodiment shown in Figure 4, its implementation principle and technical effects are similar to... Figure 2 The method shown in Figure 4 is similar to the implementation example, and will not be described in detail here.

[0205] According to embodiments of this application, this application also provides a communication device, a computer-readable storage medium, and a computer program product.

[0206] like Figure 6 As shown, Figure 6 This is a schematic diagram of the communication device provided in this application. The communication device is intended for various forms of digital computers, such as laptop computers, desktop computers, workstations, personal digital assistants, in-vehicle terminals, and other suitable computers. The components shown herein, their connections and relationships, and their functions are merely illustrative and are not intended to limit the implementation of the present application described and / or claimed herein.

[0207] like Figure 6 As shown, the communication device includes a processor 401 and a memory 402. The various components are interconnected via different buses and can be mounted on a common motherboard or installed in other ways as needed. The processor can process instructions executed within the communication device.

[0208] The memory 402 is the non-transitory computer-readable storage medium provided in this application. The memory stores instructions executable by at least one processor to cause the at least one processor to perform the crystal oscillator frequency offset determination method provided in this application. The non-transitory computer-readable storage medium of this application stores computer instructions for causing a computer to perform the crystal oscillator frequency offset determination method provided in this application.

[0209] Memory 402, as a non-transitory computer-readable storage medium, can be used to store non-transitory software programs, non-transitory computer-executable programs, and modules, such as the program instructions / modules corresponding to the crystal oscillator frequency offset determination method in the embodiments of this application (e.g., attached...). Figure 5 The first mixing module 301, the second mixing module 302, and the determination module 303 are shown. The processor 401 executes various functional applications and data processing of the communication device by running non-transient software programs, instructions, and modules stored in the memory 402, thereby implementing the crystal oscillator frequency offset determination method in the above method embodiments.

[0210] Meanwhile, a computer-readable storage medium is provided, which stores computer-executable instructions that, when executed by a processor, are used to implement the crystal oscillator frequency offset determination method of the above embodiments.

[0211] This embodiment also provides a computer product, which, when the instructions in the computer product are executed by the processor of a communication device, enables the communication device to execute the crystal oscillator frequency offset determination method of the above embodiment.

[0212] Other embodiments of the present application will readily occur to those skilled in the art upon consideration of the specification and practice of the invention disclosed herein. This application is intended to cover any variations, uses, or adaptations of the embodiments of this application that follow the general principles of the embodiments of this application and include common knowledge or customary techniques in the art not disclosed in the embodiments of this application.

[0213] It should be understood that the embodiments of this application are not limited to the precise structures described above and shown in the accompanying drawings, and various modifications and changes can be made without departing from their scope. The scope of the embodiments of this application is limited only by the appended claims.

Claims

1. A method for determining the frequency offset of a crystal oscillator, characterized in that, include: The low local oscillator carrier and the first actual signal are mixed and processed to generate a complex signal, thereby generating a first in-phase quadrature IQ complex signal. The first actual signal is the first downlink signal received when Doppler frequency offset occurs; The first IQ complex signal and the preset intermediate frequency signal are subjected to digital mixing and digital down-conversion processing to generate the corresponding first mixing result. The low local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal; The theoretical signal is the downlink signal received when no Doppler frequency offset occurs; The high-frequency carrier and the second actual signal are mixed and processed to generate a second IQ complex signal; the second actual signal is the second downlink signal received when Doppler frequency offset occurs. The second IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding second mixing result; the high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal. The first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal during reception; The first mixing result, the second mixing result, and the preset intermediate frequency are input into a preset crystal oscillator frequency offset calculation algorithm to obtain the low local oscillator (LoU) crystal oscillator offset and the high local oscillator (LO) crystal oscillator offset. The low LoU crystal oscillator offset is obtained by summing the total frequency offset of the first mixing, the total frequency offset of the second mixing, and twice the preset LO frequency, dividing by the difference between the theoretical ratio of the high and low LoU frequencies and one, and then subtracting the theoretical low LoU carrier frequency. The high LoU crystal oscillator offset is obtained by multiplying the theoretical ratio of the high and low LoU frequencies by the sum of the total frequency offset of the first mixing, the total frequency offset of the second mixing, and twice the preset LO frequency, dividing by the difference between the theoretical ratio of the high and low LoU frequencies and one, and finally subtracting the theoretical high LoU carrier frequency. The preset LO frequency is the frequency of the preset LO signal. The first mixing result, the second mixing result, the theoretical signal frequency, and the preset intermediate frequency are input into the preset Doppler frequency offset algorithm, and the Doppler frequency offset is determined by the preset Doppler frequency offset algorithm; the theoretical signal frequency is the frequency of the theoretical signal. The first mixing result, the second mixing result, the low local oscillator carrier frequency, and the preset intermediate frequency are input into the preset crystal oscillator uncertainty algorithm, and the crystal oscillator uncertainty is determined by the preset crystal oscillator uncertainty algorithm; the low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

2. The method according to claim 1, characterized in that, The step of mixing the low local oscillator carrier and the first actual signal and generating a complex signal to generate a first in-phase quadrature IQ complex signal includes: The low local oscillator carrier and the first actual signal are subjected to analog mixing to generate the first intermediate signal; The first intermediate signal is low-pass filtered to generate the second intermediate signal; An analog-to-digital converter is used to sample and process the second intermediate signal to generate the first IQ complex signal.

3. The method according to claim 1, characterized in that, The step of performing digital mixing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to generate a corresponding first mixing result includes: The first IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding third intermediate signal; The third intermediate signal is subjected to negative frequency filtering and downsampling to generate the corresponding first mixing result.

4. The method according to claim 1, characterized in that, The process of mixing the high local oscillator carrier and the second actual signal to generate a second IQ complex signal includes: The high local oscillator carrier and the second actual signal are subjected to analog mixing to generate a fourth intermediate signal; The fourth intermediate signal is low-pass filtered to generate the fifth intermediate signal; The fifth intermediate signal is sampled and processed using an analog-to-digital converter to generate the second IQ complex signal.

5. The method according to claim 1, characterized in that, The step of performing digital mixing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding second mixing result includes: The second IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate the corresponding sixth intermediate signal; The sixth intermediate signal is subjected to negative frequency filtering and downsampling to generate the corresponding second mixing result.

6. The method according to claim 1, characterized in that, After inputting the first mixing result, the second mixing result, the low local oscillator carrier frequency, and the preset intermediate frequency into a preset crystal oscillator uncertainty algorithm to determine the crystal oscillator uncertainty, the method further includes: The crystal oscillator uncertainty, Doppler frequency offset, and theoretical signal frequency are input into a preset compensation algorithm, and the preset compensation algorithm is used to generate the uplink compensation frequency. Frequency compensation is performed on the uplink signal based on the uplink compensation frequency.

7. A crystal oscillator frequency offset determination device, characterized in that, include: The first mixing module is used to mix the low local oscillator carrier and the first actual signal and perform complex signal generation processing to generate a first in-phase quadrature IQ complex signal. The first actual signal is the first downlink signal received when Doppler frequency offset occurs; The first IQ complex signal and the preset intermediate frequency signal are subjected to digital mixing and digital down-conversion processing to generate the corresponding first mixing result. The low local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal; The theoretical signal is the downlink signal received when no Doppler frequency offset occurs; The second mixing module is used to mix the high local oscillator carrier and the second actual signal and generate a complex signal to generate a second IQ complex signal; the second actual signal is the second downlink signal received when Doppler frequency offset occurs. The second IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding second mixing result; the high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal. The first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal during reception; The determining module is used to input the first mixing result, the second mixing result, and the preset intermediate frequency (IF) frequency into a preset crystal oscillator frequency offset calculation algorithm to obtain the low local oscillator (LoU) crystal oscillator offset frequency and the high local oscillator (LO) crystal oscillator offset frequency. The low LoU crystal oscillator offset frequency is obtained by summing the total frequency offset of the first mixing, the total frequency offset of the second mixing, and twice the preset IF frequency, dividing by the difference between the theoretical ratio of the high and low LoU frequencies and one, and then subtracting the theoretical low LoU carrier frequency. The high LoU crystal oscillator offset frequency is obtained by multiplying the theoretical ratio of the high and low LoU frequencies by the sum of the first mixing, the total frequency offset of the second mixing, and twice the preset IF frequency, dividing by the difference between the theoretical ratio of the high and low LoU frequencies and one, and finally subtracting the theoretical high LoU carrier frequency. The preset IF frequency is the frequency of the preset IF signal. The frequency offset determination module is used to input the first mixing result, the second mixing result, the theoretical signal frequency, and the preset intermediate frequency into a preset Doppler frequency offset algorithm, and use the preset Doppler frequency offset algorithm to determine the Doppler frequency offset; the theoretical signal frequency is the frequency of the theoretical signal; The uncertainty determination module is used to input the first mixing result, the second mixing result, the low local oscillator carrier frequency, and the preset intermediate frequency into the preset crystal oscillator uncertainty algorithm, and use the preset crystal oscillator uncertainty algorithm to determine the crystal oscillator uncertainty; the low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

8. A communication device, characterized in that, include: Memory and processor; The memory stores computer-executed instructions; The processor executes computer execution instructions stored in the memory to implement the crystal oscillator frequency offset determination method as described in any one of claims 1 to 6.

9. A computer-readable storage medium, characterized in that, The computer-readable storage medium stores computer-executable instructions, which, when executed by a processor, are used to implement the crystal oscillator frequency offset determination method as described in any one of claims 1 to 6.

10. A computer program product, comprising a computer program, characterized in that, When executed by a processor, the computer program implements the crystal oscillator frequency offset determination method as described in any one of claims 1 to 6.

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