A correction power supply device for collider beam feedback and control method thereof

Abstract

The present invention provides a correction power supply device for collider beam feedback and a control method thereof, and relates to the technical field of accelerator magnet power supply. The correction power supply device comprises: a control module and a plurality of full-bridge circuits connected in parallel; the full-bridge circuit comprises a power supply module and a full-bridge conversion module; the voltage input end of the full-bridge conversion module is connected to the power supply module; the voltage output end of the full-bridge conversion module is connected to the magnet load; the control module is used to apply the carrier phase shifting technology to determine the driving signals of the plurality of switch tubes included in the full-bridge conversion module; the full-bridge conversion module is used to control the conduction and shutdown of the plurality of switch tubes according to the duty cycle and phase shift angle of the driving signal, and convert the DC output of the power supply module into a preset output. The present invention improves the rapidity of the correction power supply operation by connecting a plurality of full-bridge circuits in parallel, and also improves the equivalent switching frequency of the input end of the magnet load by applying the carrier phase shifting technology, thereby improving the stability of the correction power supply operation.

Description

Technical Field

[0001] The present invention relates to the technical field of accelerator magnet power supply, and more specifically, to a correction power supply device for collider beam feedback and a control method thereof. Background Art

[0002] The collision point feedback system of the super-taochan device is used to maintain the stable operation of the particle beam in the collider. Due to the magnetic field, thermal effects and other unstable factors inside the accelerator, the particle beam will deviate from the ideal orbit. The orbit feedback system monitors the deviation of the beam in real time and corrects it to ensure the accurate collision of the particle beam at the collision point. Since the particle beam density and energy of the super-taochan device are extremely high, the real-time and accuracy of the collision point feedback system are particularly important, so the fast correction magnet power supply is required to have high bandwidth and low ripple characteristics. The rapid response capability of the power supply can be improved by increasing the input voltage, but a larger input voltage will increase the output ripple of the power supply, thereby reducing the accuracy of the system; in order to improve the accuracy of the system, it can be achieved by increasing the parameters of the output filter, but it will reduce the bandwidth of the system and affect the dynamic response performance.

[0003] The traditional full-bridge converter consists of two bridge arms and can achieve bipolar output. By increasing the input voltage of the full-bridge circuit, its fast response performance can be improved. However, increasing the input voltage will inevitably lead to an increase in the ripple of the output current, which poses a challenge to the design of the output filter. Increasing the filter parameters can reduce the ripple of the output current, but it will reduce the dynamic response of the full-bridge converter. Therefore, it is urgent to design a new type of fast correction magnet power supply for the collision point feedback system, which can reduce the output current ripple while increasing the dynamic response performance of the power supply to meet the requirements of the collision point feedback system. Summary of the invention

[0004] In view of this, the present invention provides a correction power supply device for collider beam feedback and a control method thereof.

[0005] One aspect of the present invention provides a correction power supply device for collider beam feedback, comprising: a control module and a plurality of full-bridge circuits connected in parallel.

[0006] The full-bridge circuit comprises a power module and a full-bridge conversion module; the voltage input end of the full-bridge conversion module is connected to the power module; the voltage output end of the full-bridge conversion module is connected to the magnetic load.

[0007] The control module is connected to the full-bridge conversion module; the control module is used to determine the driving signals of the multiple switch tubes included in the full-bridge conversion module by applying the carrier phase shifting technology.

[0008] The full-bridge conversion module is used to control the on and off of the multiple switch tubes according to the duty cycle and phase shift angle of the drive signal, convert the DC output of the power module into a preset output, and input the preset output into the magnetic load.

[0009] According to an embodiment of the present invention, the full-bridge conversion module includes a full-bridge converter and a filter circuit; the input end of the full-bridge converter is connected to the power supply module; the output end of the full-bridge converter is connected to the input end of the filter circuit; and the output end of the filter circuit is connected to the magnetic load.

[0010] According to an embodiment of the present invention, the full-bridge converter comprises a plurality of bridge arms connected in parallel, the plurality of bridge arms comprise a plurality of output bridge arms and one input bridge arm, and the filtering circuit comprises at least one passive filtering unit.

[0011] Each of the bridge arms comprises an upper bridge arm and a lower bridge arm connected in series; each of the upper bridge arm and the lower bridge arm comprises a switch tube.

[0012] The midpoint of each of the output bridge arms is connected to the first input end of one of the passive filter units; the midpoint of the input bridge arm is connected to the respective second input end of at least one of the passive filter units.

[0013] The output end of each of the at least one passive filtering unit is connected in parallel with the magnetic load; wherein, the output end of each of the at least one passive filtering unit is the output end of the filtering circuit.

[0014] According to an embodiment of the present invention, the passive filtering unit includes a filtering inductor and a filtering capacitor.

[0015] One end of the filter inductor is the first input end; the other end of the filter inductor is connected to one end of the filter capacitor and also to one end of the magnetic load.

[0016] The other end of the filter capacitor is connected to the midpoint of the input bridge arm and is also connected to the other end of the magnetic load.

[0017] According to an embodiment of the present invention, the control module includes a sampling unit and a controller unit.

[0018] The sampling unit is arranged at the connection end between the full-bridge conversion module and the magnetic load; the sampling unit is used to collect the current value and the voltage value of the magnetic load.

[0019] The above-mentioned controller unit is connected to the above-mentioned sampling unit and the above-mentioned full-bridge conversion module respectively; the above-mentioned controller unit is used to generate a driving signal for the above-mentioned switch tube according to the above-mentioned current value and the above-mentioned voltage value to control the opening and closing of the above-mentioned switch tube, so that the above-mentioned full-bridge circuit outputs the above-mentioned preset output.

[0020] According to an embodiment of the present invention, the controller unit includes a PID controller and a PWM wave generator.

[0021] The PID controller is used to generate the amplitude of the modulation wave of the PWM wave generator according to the current value and the voltage value.

[0022] The PWM wave generator is used to generate the driving signal according to the amplitude of the modulation wave.

[0023] According to an embodiment of the present invention, the sampling unit includes a voltage sampler, a current sampler and an A / D conversion module.

[0024] The voltage sampler and the current sampler are both connected to the controller unit via the A / D conversion module.

[0025] According to an embodiment of the present invention, the A / D conversion module is connected to the controller unit via an SPI protocol.

[0026] Another aspect of the present invention provides a control method for a correction power supply device for collider beam feedback, comprising: obtaining the actual direct current output by the full-bridge circuit.

[0027] According to the difference between the actual direct current and the reference current, the on-time and off-time of each of the multiple switch tubes included in the full-bridge conversion module are determined.

[0028] According to the number of the full-bridge circuits and the number of the multiple switch tubes included in the full-bridge conversion module, a carrier phase shifting technique is applied to determine the turn-on time and turn-off time of each of the multiple switch tubes.

[0029] The driving signals of the respective multiple switch tubes are determined according to the above-mentioned on-time and the above-mentioned off-time and the above-mentioned on-time and the above-mentioned off-time, so that the above-mentioned full-bridge circuit outputs a preset output; wherein the driving signal includes a duty cycle and a phase shift angle; the duty cycle is determined according to the on-time and the off-time; the phase shift angle is determined according to the on-time and the off-time.

[0030] According to an embodiment of the present invention, the above-mentioned carrier phase shifting technology is applied according to the number of the above-mentioned full-bridge circuits and the number of multiple switching tubes included in the above-mentioned full-bridge converter to determine the phase shift angle of the driving signal of each of the above-mentioned multiple switching tubes, including: the number of the above-mentioned full-bridge circuits is N, the above-mentioned full-bridge conversion module includes M-1 output bridge arms and 1 input bridge arm, each of the above-mentioned output bridge arms includes an upper bridge arm and a lower bridge arm connected in series; the upper bridge arm of the above-mentioned output bridge arm includes a switching tube; the lower bridge arm of the above-mentioned output bridge arm includes a switching tube; the above-mentioned input bridge arm includes an upper bridge arm and a lower bridge arm connected in series; the upper bridge arm of the above-mentioned input bridge arm includes a switching tube; the lower bridge arm of the above-mentioned input bridge arm includes a switching tube.

[0031] The phase shift angle between the j-1th output bridge arm of the ith full-bridge circuit and the jth output bridge arm of the ith full-bridge circuit is 360° / (M-1).

[0032] The phase shift angle between the j-1th output bridge arm of the i-1th full-bridge circuit and the j-1th output bridge arm of the i-th full-bridge circuit is 360° / (N×(M-1)); wherein i is a positive integer greater than 1 and less than or equal to N; and j is a positive integer greater than 1 and less than or equal to M-1.

[0033] According to an embodiment of the present invention, since multiple full-bridge circuits are connected in parallel in the correction power supply device, the output current of each full-bridge circuit is input in parallel to the magnet load, so that the current is superimposed and input to the magnet load, thereby improving the dynamic response of the correction power supply device; in addition, the control module applies the carrier phase shifting technology to determine the drive signals of the multiple switch tubes included in the full-bridge conversion module, and the full-bridge conversion module controls the conduction and shutdown of the multiple switch tubes according to the duty cycle and phase shift angle of the drive signal. Without increasing the switching frequency of a single switch tube, the equivalent switching frequency of the input end of the magnet load is increased, which greatly overcomes the influence of the switching frequency on the ripple size, increases the stability of the current output, and realizes the control of the ripple of the current output by the correction power supply device, at least partially overcomes the technical problem in the prior art that increasing the filter parameters can reduce the ripple of the output current, but will reduce the dynamic response of the full-bridge converter, thereby achieving the technical effect of effectively improving the rapidity and stability of the correction power supply. BRIEF DESCRIPTION OF THE DRAWINGS

[0034] The above and other objects, features and advantages of the present invention will become more apparent through the following description of the embodiments of the present invention with reference to the accompanying drawings.

[0035] Figure 1 A module diagram of a correction power supply device for collider beam feedback according to an embodiment of the present invention is shown.

[0036] Figure 2A module diagram showing the connection relationship of a full-bridge circuit in a correction power supply device according to an embodiment of the present invention is shown.

[0037] Figure 3 The structure block diagram of a correction power supply device including two full-bridge converters according to an embodiment of the present invention is shown.

[0038] Figure 4 A block diagram showing the connection relationship of control modules according to an embodiment of the present invention is shown.

[0039] Figure 5 A flow chart of a control method for calibrating a power supply device according to an embodiment of the present invention is shown.

[0040] Figure 6 A schematic diagram of driving waveforms of switch tubes in a correction power supply device including two full-bridge converters according to an embodiment of the present invention is shown.

[0041] Figure 7 A schematic diagram of an output current waveform obtained by simulation of a correction power supply device including two full-bridge converters according to an embodiment of the present invention is shown.

[0042] Figure 8 The figure shows a schematic diagram of the output current waveform of a correction power supply device including two full-bridge converters according to an embodiment of the present invention when a maximum step signal of 0.05A is applied for simulation. DETAILED DESCRIPTION

[0043] Below, embodiments of the present invention will be described with reference to the accompanying drawings. However, it should be understood that these descriptions are exemplary only and are not intended to limit the scope of the present invention. In the following detailed description, for ease of explanation, many specific details are set forth to provide a comprehensive understanding of embodiments of the present invention. However, it is apparent that one or more embodiments may also be implemented without these specific details. In addition, in the following description, descriptions of known structures and technologies are omitted to avoid unnecessary confusion of concepts of the present invention.

[0044] The terms used herein are only for describing specific embodiments and are not intended to limit the present invention. The terms "comprise", "include", etc. used herein indicate the existence of the features, steps, operations and / or components, but do not exclude the existence or addition of one or more other features, steps, operations or components.

[0045] All terms (including technical and scientific terms) used herein have the meanings commonly understood by those skilled in the art unless otherwise defined. It should be noted that the terms used herein should be interpreted as having a meaning consistent with the context of this specification and should not be interpreted in an idealized or overly rigid manner.

[0046] When using expressions such as "at least one of A, B, and C, etc.", they should generally be interpreted according to the meaning of the expression commonly understood by those skilled in the art (for example, "a system having at least one of A, B, and C" should include but is not limited to a system having A alone, B alone, C alone, A and B, A and C, B and C, and / or A, B, C, etc.).

[0047] An embodiment of the present invention provides a correction power supply device for collider beam feedback and a control method thereof.

[0048] Figure 1 A module diagram of a correction power supply device for collider beam feedback according to an embodiment of the present invention is shown.

[0049] like Figure 1 As shown, the correction power supply device for collider beam feedback includes: a control module and multiple full-bridge circuits connected in parallel. The full-bridge circuit includes a power module and a full-bridge conversion module; the voltage input end of the full-bridge conversion module is connected to the power module; the voltage output end of the full-bridge conversion module is connected to the magnetic load; the control module is connected to the full-bridge conversion module; the control module is used to apply the carrier phase shifting technology to determine the driving signal of multiple switch tubes included in the full-bridge conversion module. The full-bridge conversion module is used to control the conduction and shutdown of multiple switch tubes according to the duty cycle and phase shift angle of the driving signal, convert the DC output of the power module into a preset output, and input the preset output into the magnetic load.

[0050] According to an embodiment of the present invention, since a plurality of full-bridge circuits are connected in parallel in the correction power supply device, the output current of each full-bridge circuit is input in parallel to the magnet load, so that the current is superimposed and input to the magnet load, thereby improving the dynamic response of the correction power supply device; in addition, the driving signal of the plurality of switch tubes included in the full-bridge conversion module is transmitted through the control module to control the duty cycle and phase shift angle of the plurality of switch tubes, thereby being able to control the switching sequence of each switch tube of all full-bridge circuits within one switching cycle, thereby achieving control of the ripple of the current output by the correction power supply device, at least partially overcoming the technical problem in the prior art that increasing the filter parameters can reduce the ripple of the output current, but will reduce the dynamic response of the full-bridge converter, thereby achieving the technical effect of effectively improving the rapidity and stability of the correction power supply.

[0051] In addition, the present invention reduces the complexity of the circuit of the correction power supply device and simplifies the circuit structure by connecting multiple full-bridge circuits in parallel. By adopting a full-bridge conversion module, compared with a cascaded asynchronous buck circuit, it reduces the working switching loss and increases the switching frequency of the switching tube, thereby effectively improving the speed and stability of the correction magnet power supply.

[0052] According to an embodiment of the present invention, the full-bridge conversion module includes a full-bridge converter and a filter circuit; the input end of the full-bridge converter is connected to the power module; the output end of the full-bridge converter is connected to the input end of the filter circuit; and the output end of the filter circuit is connected to the magnetic load.

[0053] Reference below Figure 2 , combined with specific embodiments Figure 1 The corrected power supply device shown is further explained.

[0054] Figure 2 A module diagram showing the connection relationship of a full-bridge circuit in a correction power supply device according to an embodiment of the present invention is shown.

[0055] like Figure 2 As shown, the power supply module can be a switching power supply that converts the industrial frequency AC voltage into a DC input voltage. The full-bridge converter can control the on and off of the switch tube of the full-bridge converter according to the drive signal generated by the control module. Each switch tube is connected to the control module and receives the drive signal sent by the control module. The drive signals of different switch tubes can be different. The drive signal output by the control module can be set according to the actual situation. The full-bridge converter transmits the DC voltage to the filter circuit, and the filter circuit is used to convert the input high-frequency DC voltage signal into a stable DC signal, and output it to the magnetic load connected to the filter circuit, so that the magnetic load can obtain a reference current. Among them, the filter circuit can be a variety of types of filters, for example, the filter circuit is a passive filter.

[0056] According to an embodiment of the present invention, a full-bridge converter includes a plurality of bridge arms connected in parallel, the plurality of bridge arms include a plurality of output bridge arms and an input bridge arm, and the filter circuit includes at least one passive filter unit; each bridge arm includes an upper bridge arm and a lower bridge arm connected in series; the upper bridge arm and the lower bridge arm each include a switch tube; the midpoint of each output bridge arm is connected to the first input end of a passive filter unit; the midpoint of the input bridge arm is connected to the respective second input end of at least one passive filter unit; the respective output end of at least one passive filter unit is connected in parallel with the magnetic load. Wherein, the respective output end of at least one passive filter unit is the output end of the filter circuit.

[0057] According to an embodiment of the present invention, the passive filtering unit includes a filter inductor and a filter capacitor; one end of the filter inductor is a first input end; the other end of the filter inductor is respectively connected to one end of the filter capacitor and one end of the magnetic load; the other end of the filter capacitor is respectively connected to the midpoint of the input bridge arm and the other end of the magnetic load.

[0058] For example, each full-bridge circuit includes a power module and a full-bridge converter, N full-bridge circuits include N power modules and N full-bridge converters, N≥2, N full-bridge converters are independently connected to the N power modules, each full-bridge converter includes M bridge arms and M-1 filter circuits, M≥3, the M bridge arms are connected in parallel at both ends of the bus of each full-bridge converter, one end of the M-1 filter circuits is respectively connected to the midpoint of the first M-1 bridge arms, that is, the midpoint of the output bridge arm, and the other end is all connected to the midpoint of the Mth bridge arm, that is, the midpoint of the input bridge arm, and all filter circuits are connected in parallel at both ends of the magnetic load.

[0059] The present invention reduces the output ripple of the correction power supply device by adopting a full-bridge converter with multiple bridge arms, improves the dynamic response speed of the correction power supply device by connecting multiple full-bridge converters in parallel, and effectively improves the rapidity and stability of the magnet power supply, which can meet the characteristic requirements of fast correction magnets for fast dynamic response and low ripple.

[0060] Reference below Figure 3 , combined with specific embodiments Figure 1 and Figure 2 The full-bridge circuit of the correction power supply device shown is further explained.

[0061] Figure 3 The structure block diagram of a correction power supply device including two full-bridge converters according to an embodiment of the present invention is shown.

[0062] like Figure 3 As shown, the correction power supply device can select two full-bridge circuits; Figure 3 In, S 11 , S 12 , S 13 , S 14 , S 15 and S 16 The full-bridge converter in which it is located is the full-bridge converter in the first full-bridge circuit; S 21 , S 22 , S 23 , S 24 , S 25 and S 26 The full-bridge converter is the full-bridge converter in the second full-bridge circuit. 11 , S 12 , S 13 , S 14 , S 15 and S 16 and S 21 , S 22 , S 23 , S 24 , S 25 and S 26They are all switch tubes. There are many types of switch tubes to choose from, and you can choose a switch tube with new wide bandgap semiconductor technology. For example, if you choose gallium nitride (GaN) MOSFET as the switch tube, you can ensure the fast dynamic response and low ripple characteristics of the correction power supply device. The use of switch tubes with new wide bandgap semiconductor technology can greatly increase the switching frequency, reduce switching losses, and improve power efficiency.

[0063] exist Figure 3 In the full-bridge converter, three bridge arms are connected to each other, of which the first two bridge arms are output bridge arms. Since the four switch tubes of the output bridge arm work in a high-speed switching state, the output bridge arm is also called a high-frequency bridge arm. The last bridge arm is the input bridge arm. The two switch tubes of the input bridge arm work in a long-term on or long-term off state, and only change when the current direction changes, which is called a low-frequency bridge arm. 11 With S 13 It is the upper bridge arm of the two high-frequency bridge arms of the first full-bridge converter; S 12 With S 14 It is the lower bridge arm of the two high-frequency bridge arms of the first full-bridge converter; S 21 With S 23 It is the upper bridge arm of the two high-frequency bridge arms of the second full-bridge converter; S 22 With S 24 It is the lower bridge arm of the two high-frequency bridge arms of the second full-bridge converter. 15 With S 25 is the upper arm of the low-frequency bridge arm, S 16 With S 26 It is the lower bridge arm of the low-frequency bridge arm. When the direction of the current is positive, the upper tube of the low-frequency bridge arm is turned off and the lower tube of the low-frequency bridge arm is turned on; when the direction of the current is negative, the upper tube of the low-frequency bridge arm is turned on and the lower tube of the low-frequency bridge arm is turned off. Each full-bridge converter is connected to two filter circuits, one end of each filter circuit is connected to the midpoint of a different high-frequency bridge arm, and the other end is connected to the midpoint of the low-frequency bridge arm. Different filter parameters can be set for the filter circuit through the characteristics of the magnetic load, that is, the parameters of the filter inductor and the filter capacitor.

[0064] The following is a more detailed description taking the first full-bridge circuit as an example. The second full-bridge circuit has the same structure as the first full-bridge circuit and will not be described in detail.

[0065] In the first full-bridge circuit, S 11 and S 12 The first output bridge arm, S 13 and S 14 The second output bridge arm, S 15 and S 16 The input bridge arm is formed; the filter circuit is selected as a passive filter, which can be an LC filter. The LC filter is further described below.

[0066] S 11 and S 12 The connection point is connected to one end of the input end of the LC filter, and the LC filter serves as the first filtering circuit, S 15 and S 16 The connection point is connected to the other end of the input end of the first filter circuit, that is, the filter inductor L of the first filter circuit 11 One end of S 11 and S 12 The connection point is connected to one end of the filter capacitor of the first filter circuit and S 15 and S 16 The other end of the filter inductor of the first filter circuit is connected to the other end of the filter capacitor; the other end of the filter inductor of the first filter circuit is also connected to one end of the magnetic load; the other end of the filter capacitor of the first filter circuit is also connected to the other end of the magnetic load.

[0067] The connection point between the upper bridge arm and the lower bridge arm is the midpoint of the bridge arm. 11 and S 12 The connection point, i.e., point A, is the midpoint of the first output bridge arm of the first full-bridge circuit. Point A is connected to one end of the input end of the LC filter. The LC filter serves as the first filtering circuit, i.e., point L 11 One end of L is connected to point A. 11 The other end of the 11 One end of the magnet load is also connected to C 11 The other end of S 15 and S 16 The connection point D 1 connection, and also connect the other end of the magnet load.

[0068] S 13 and S 14 The connection point is connected to one end of the input end of another LC filter, and the LC filter serves as the second filtering circuit, S 15 and S 16 The connection point of is connected to the other end of the input end of the second filter circuit, that is, one end of the filter inductor of the second filter circuit and S 13 and S 14 The connection point of the second filter circuit is connected to one end of the filter capacitor and S 15 and S 16 The other end of the filter inductor of the second filter circuit is connected to the other end of the filter capacitor; the other end of the filter inductor of the second filter circuit is also connected to one end of the magnetic load; the other end of the filter capacitor of the second filter circuit is also connected to the other end of the magnetic load.

[0069] S 13and S 14 The connection point, that is, point B, is the midpoint of the second output bridge arm of the first full-bridge circuit. Point A is connected to one end of the input end of another LC filter, which serves as the second filtering circuit, that is, L 12 One end of L is connected to point B, 12 The other end of the 12 One end of the magnet load is also connected to C 12 The other end of S 15 and S 16 The connection point D 2 Connect to the other end of the magnet load. 1 and D 2 All S 15 and S 16 The connection point, that is, S 15 and S 16 The midpoint of S 15 and S 16 The midpoint is Figure 3 Displayed as D 1 Point and D 2 point.

[0070] The magnet amplitude is equivalent to an inductive load and a resistive load connected in series, C 12 One end of the inductive load is connected to one end of the inductive load, the other end of the inductive load is connected to the resistive load, and the other end of the resistive load is connected to C 12 The other end of the connection; C 11 One end of the inductive load is connected to one end of the inductive load, the other end of the inductive load is connected to the resistive load, and the other end of the resistive load is connected to C 11 The other end of the connection.

[0071] The voltage input terminal of the full-bridge conversion module and the input terminal of the full-bridge converter are both S 11 , S 12 , S 13 , S 14 , S 15 and S 16 The voltage input terminal. C 11 One end of the magnet load is connected to the other end of the magnet load. 11 The other end of the magnet load is connected to the other end of the magnet load. 12 One end of the magnet load is connected to the other end of the magnet load. 12 The other end of C is connected to the other end of the magnet load. 11 Both ends and C 12 Both ends of are the voltage output terminals of the full-bridge variable module. Point A, Point B, Point D 1 Point and D 2Point is the output end of the full-bridge converter. In the first full-bridge circuit, one end of the DC voltage output end of the power module is connected to S 11 , S 13 and S 15 The other end of the DC voltage output terminal of the power module is connected to S 12 , S 14 and S 16 The source connection of S 11 , S 13 and S 15 The drain and S 12 , S 14 and S 16 The source is the voltage input terminal of the full-bridge change module and the input terminal of the full-bridge converter. The DC voltage output by the power module can be set according to actual needs. For example, the DC voltage output terminal of the power module provides a +12V voltage.

[0072] According to an embodiment of the present invention, the control module includes a sampling unit and a controller unit; the sampling unit is arranged at the connection end between the full-bridge conversion module and the magnetic load; the sampling unit is used to collect the current value and the voltage value of the magnetic load; the controller unit is respectively connected to the sampling unit and the full-bridge conversion module; the controller unit is used to generate a driving signal of the switch tube according to the current value and the voltage value to control the opening and closing of the switch tube, so that the full-bridge circuit outputs a preset output.

[0073] Reference below Figure 4 , combined with specific embodiments Figure 1 and Figure 2 The full-bridge circuit of the correction power supply device shown is further explained.

[0074] Figure 4 A block diagram showing the connection relationship of control modules according to an embodiment of the present invention is shown.

[0075] like Figure 4 As shown, the control module includes a sampling unit and a controller unit; the controller unit includes a PID controller and a PWM wave generator. The PID controller is used to generate the amplitude of the modulation wave of the PWM wave generator according to the current value and the voltage value; the PWM wave generator is used to generate a driving signal according to the amplitude of the modulation wave.

[0076] For example, the sampling unit includes a voltage sampler, a current sampler and an A / D conversion module. The voltage sampler and the current sampler are connected to the controller unit through the A / D conversion module. The A / D conversion module is connected to the controller unit through the SPI protocol. Among them, the current sampler can be connected in series with the magnet load to collect the current value flowing into the magnet load. For example, the current sampler can select a high-performance Hall current sensor to convert the large current flowing through the magnet load into a small current of 4mA-20mA. The voltage sampler is connected in parallel with the magnet load to collect the voltage value at both ends of the magnet load. The voltage sampler can select a high-precision and low-temperature drift precision sampling resistor. For example, the sampling resistor is a low-temperature drift precision sampling resistor with a temperature coefficient of less than 5ppm / ℃. The controller unit can be implemented using an FPGA chip. The A / D conversion module can be implemented through an ADC sampling chip to convert the current value and voltage value analog signals obtained by the sampling unit into digital signals that can be operated by the FPGA. For example, the A / D conversion module can use two 18-bit ADC chips. The FPGA chip obtains the data sampled by the ADC through the SPI protocol, calculates the duty cycle of the PWM wave through the filtering algorithm and the PID algorithm, and outputs the PWM wave to the switch tube of the full-bridge converter of each full-bridge circuit to control the on and off of the switch tube, thereby controlling the current. Among them, the filtering algorithm can be implemented using the built-in filtering algorithm of the FPGA chip, which is used to filter out the noise signal received due to EMI interference in the digital signal output by the A / D conversion module, and restore the actual real current value digital signal and voltage value digital signal.

[0077] exist Figure 4 In, L load represents the equivalent inductance of the magnet load, R represents the equivalent resistance of the magnet load, V load Represents the voltage across the magnet load, I load Represents the input current of the magnet load, PWM is Pulse Width Modulation, and its Chinese name is pulse width modulation. PID controller is PID controller, where PID is Proportion Integration Differentiation, and its Chinese name is proportional integral differential, I ref Stands for reference current; A / D stands for Analog-to-digital converter, and its Chinese name is analog-to-digital converter. SPI stands for Serial Peripheral Interface, and its Chinese name is serial peripheral interface.

[0078] Combination Figure 3The circuit sampler is arranged between the connection point of the other end of the filter inductor and the other end of the filter capacitor of the first filter circuit and one end of the magnet load. The control module processes and calculates the sampled voltage and current values, and transmits the obtained driving signals to each switch tube of the full-bridge converter to control the on and off of the switch tube, thereby controlling the direction and magnitude of the output current of the bridge circuit in real time.

[0079] The present invention also provides a control method for a correction power supply device for collider beam feedback.

[0080] Figure 5 A flow chart of a control method for calibrating a power supply device according to an embodiment of the present invention is shown.

[0081] like Figure 5 As shown, the control method includes operations S501 to S504.

[0082] In operation S501 , an actual direct current output by the full-bridge circuit is obtained.

[0083] In operation S502, the on-time and off-time of each of the plurality of switch tubes included in the full-bridge conversion module are determined according to the difference between the actual direct current and the reference current.

[0084] In operation S503, according to the number of full-bridge circuits and the number of multiple switch tubes included in the full-bridge conversion module, a carrier phase shifting technique is applied to determine the turn-on time and turn-off time of each of the multiple switch tubes.

[0085] In operation S504, the driving signals of the multiple switch tubes are determined according to the on-time and the off-time and the on-time and the off-time, so that the full-bridge circuit outputs a preset output; wherein the driving signal includes a duty cycle and a phase shift angle; the duty cycle is determined according to the on-time and the off-time; the phase shift angle is determined according to the on-time and the off-time.

[0086] Exemplarily, the current value digital signal collected by the current sampler is compared with the reference current to obtain the current difference, and the difference data is input into the PID controller. After calculation by the PID controller, the modulation wave amplitude of the current PWM signal is obtained, and the amplitude is modulated with a specific carrier, and the generated square wave is the waveform of the current PWM. Among them, the size of the reference current can be set according to the actual situation. As the current flowing through the magnet load continues to change, the output current is finally infinitely close to the reference current size under the regulation of the closed-loop control composed of the full-bridge circuit and the control module, and the closed-loop control of the correction power supply device is realized. Through the closed-loop control of the on-time and off-time of each switch tube, and the on-time and off-time of each switch tube are controlled, the on-time and off-time correspond to the duty cycle of each PWM wave, and the on-time and off-time correspond to the phase shift angle of each PWM wave. Among them, the collected voltage value is used for limiting and protection. When the output voltage of the correction power supply device is too large, the output voltage can be reduced by adjusting the duty cycle of the PWM wave. When the correction power supply device enters a stable state, the voltage feedback loop exits the saturation state, and the voltage feedback does not work. For example, when the correction power supply device is turned on, the overshoot is obvious, causing the output voltage of the full-bridge circuit to be too large. At this time, the voltage feedback works to adjust the duty cycle of the PWM wave and reduce the output voltage of the full-bridge circuit.

[0087] Exemplarily, the control module can also realize remote operation through hardware, for example, realize host computer control through RS232 serial port protocol, set reference current, set protection voltage threshold, and check voltage and current in real time.

[0088] According to an embodiment of the present invention, the number of full-bridge circuits is N, and the full-bridge conversion module includes M-1 output bridge arms and 1 input bridge arm, each output bridge arm includes an upper bridge arm and a lower bridge arm connected in series; the upper bridge arm of the output bridge arm includes a switching tube; the lower bridge arm of the output bridge arm includes a switching tube; the input bridge arm includes an upper bridge arm and a lower bridge arm connected in series; the upper bridge arm of the input bridge arm includes a switching tube; and the lower bridge arm of the input bridge arm includes a switching tube.

[0089] The phase shift angle between the j-1th output bridge arm of the i-th full-bridge circuit and the j-1th output bridge arm of the i-th full-bridge circuit is 360° / (M-1). The phase shift angle between the j-1th output bridge arm of the i-1th full-bridge circuit and the j-1th output bridge arm of the i-th full-bridge circuit is 360° / (N×(M-1)); where i is a positive integer greater than 1 and less than or equal to N; j is a positive integer greater than 1 and less than or equal to M-1.

[0090] Figure 6 A schematic diagram of driving waveforms of switch tubes in a correction power supply device including two full-bridge converters according to an embodiment of the present invention is shown.

[0091] like Figure 3 and Figure 6 As shown, the phase difference of the output bridge arms in the same full-bridge converter is 360° / (M-1), that is, 180°; the phase difference of the output bridge arms in different full-bridge converters is 360° / (N×(M-1)), that is, 90°. 12 , S 14 , S 22 , S 24 The driving signals of the upper bridge arm are complementary to those of the upper bridge arm. When the output current direction is positive, the upper bridge arm of all input bridge arms, that is, S 15 With S 25 All the lower bridge arms of the input bridge arms, i.e. S 16 With S 26 When the output current is negative, the switching state of the input bridge arm is opposite. Figure 6 In the figure, T represents period and CLK represents clock.

[0092] Compared with the magnet power supply of the traditional full-bridge converter, the present invention optimizes the topological structure and connects the output ends of multiple full-bridge converters in parallel, so that the equivalent switching frequency of the output end can be increased by (N×(M-1)) times without increasing the switching frequency, simplifying the design of the filter circuit and reducing the output ripple; and adopting a phase-shift modulation method to make the output of the full-bridge circuit more accurate, the switch tubes of the same bridge arm are alternately and complementary turned on, the dead time is increased to avoid crosstalk, and the reliability of the power supply is improved; in addition, since gallium nitride MOSFET is used in the full-bridge converter of the present invention, and gallium nitride MOSFET has no body diode connected in parallel with MOSFET due to the superior characteristics of its material, and there is no reverse recovery loss, gallium nitride MOSFET can achieve a higher frequency switching speed, further improve the switching frequency of the full-bridge converter, and further improve the dynamic response characteristics of the magnet power supply.

[0093] Figure 7 A schematic diagram of an output current waveform obtained by simulation of a correction power supply device including two full-bridge converters according to an embodiment of the present invention is shown.

[0094] like Figure 7 As shown, the switching frequency of the switch tube is 100kHz, and the load magnet inductance is 3mH. Due to the staggered conduction of multiple bridge arms and the parallel output of multiple full-bridge converters, the switching frequency equivalent to the output end is f s × (N × (M-1)), that is, 400kHz, where the horizontal axis is time and the vertical axis is current. Figure 7 It can be seen that the output current ripple is less than 10ppm, which meets the design requirements for ripple.

[0095] Figure 8 The figure shows a schematic diagram of the output current waveform of a correction power supply device including two full-bridge converters according to an embodiment of the present invention when a maximum step signal of 0.05A is applied for simulation.

[0096] like Figure 8 As shown in FIG. 1 , a correction power supply device including two full-bridge converters is tested when a maximum step signal of 0.05A is applied. The maximum response time of the correction magnet power supply is 150us, and the dynamic response performance meets the design requirements. Figure 8 In the figure, the horizontal axis is time and the vertical axis is current.

[0097] In the present invention, a plurality of full-bridge circuits are connected in parallel in the correction power supply device, and the output current of each full-bridge circuit is input in parallel to the magnet load, so that the current is superimposed and input to the magnet load, thereby improving the dynamic response of the correction power supply device; and because a phase-shifted carrier control strategy is adopted, the equivalent switching frequency of the input end of the magnet load is increased by (N×(M-1)) times without increasing the switching frequency of a single switch tube, thereby greatly overcoming the influence of the switching frequency on the ripple size, increasing the stability of the current output, simplifying the design of the output filter, reducing the parameters of the output filter, and further solving the problem of slow dynamic response of the correction power supply due to excessive filter parameters, thereby achieving the technical effect of effectively improving the rapidity and stability of the correction power supply.

[0098] The embodiments of the present invention are described above. However, these embodiments are only for the purpose of illustration, and are not intended to limit the scope of the present invention. Although each embodiment is described above, it does not mean that the measures in each embodiment cannot be used in combination advantageously. Without departing from the scope of the present invention, those skilled in the art may make various substitutions and modifications, which should all fall within the scope of the present invention.

Claims

1. A correction power supply device for collider beam feedback, characterized in that: The correction power supply device comprises: a control module and a plurality of full-bridge circuits connected in parallel; The full-bridge circuit includes a power module and a full-bridge conversion module; the voltage input end of the full-bridge conversion module is connected to the power module; the voltage output end of the full-bridge conversion module is connected to the magnetic load; The control module is connected to the full-bridge conversion module; the control module is used to determine the driving signals of multiple switch tubes included in the full-bridge conversion module by applying carrier phase shift technology; The full-bridge conversion module is used to control the on and off of the multiple switch tubes according to the duty cycle and phase shift angle of the driving signal, convert the DC output of the power module into a preset output, and input the preset output into the magnetic load; The number of the full-bridge circuits is N, and the full-bridge conversion module includes M-1 output bridge arms and 1 input bridge arm, each of the output bridge arms includes an upper bridge arm and a lower bridge arm connected in series; the upper bridge arm of the output bridge arm includes a switch tube; the lower bridge arm of the output bridge arm includes a switch tube; the input bridge arm includes an upper bridge arm and a lower bridge arm connected in series; the upper bridge arm of the input bridge arm includes a switch tube; the lower bridge arm of the input bridge arm includes a switch tube; The phase shift angle between the j-1th output bridge arm of the ith full-bridge circuit and the jth output bridge arm of the ith full-bridge circuit is 360° / (M-1); The phase shift angle between the j-1th output bridge arm of the i-1th full-bridge circuit and the j-1th output bridge arm of the i-th full-bridge circuit is 360° / (N×(M-1)); wherein i is a positive integer greater than 1 and less than or equal to N; and j is a positive integer greater than 1 and less than or equal to M-1.

2. The correction power supply device for collider beam feedback according to claim 1, characterized in that: The full-bridge conversion module includes a full-bridge converter and a filter circuit; the input end of the full-bridge converter is connected to the power module; the output end of the full-bridge converter is connected to the input end of the filter circuit; and the output end of the filter circuit is connected to the magnetic load.

3. The correction power supply device for collider beam feedback according to claim 2, characterized in that: The full-bridge converter comprises a plurality of bridge arms connected in parallel, the plurality of bridge arms comprises a plurality of output bridge arms and an input bridge arm, and the filtering circuit comprises at least one passive filtering unit; Each of the bridge arms comprises an upper bridge arm and a lower bridge arm connected in series; each of the upper bridge arm and the lower bridge arm comprises a switch tube; The midpoint of each of the output bridge arms is connected to the first input terminal of one of the passive filtering units; the midpoint of the input bridge arm is connected to the respective second input terminal of at least one of the passive filtering units; The output end of each of the at least one passive filtering unit is connected in parallel with the magnetic load; wherein the output end of each of the at least one passive filtering unit is the output end of the filtering circuit.

4. The correction power supply device for collider beam feedback according to claim 3, characterized in that: The passive filtering unit includes a filtering inductor and a filtering capacitor; One end of the filter inductor is the first output end; the other end of the filter inductor is connected to one end of the filter capacitor and also connected to one end of the magnetic load; The other end of the filter capacitor is connected to the midpoint of the input bridge arm and is also connected to the other end of the magnetic load.

5. The correction power supply device for collider beam feedback according to claim 1, characterized in that: The control module includes a sampling unit and a controller unit; The sampling unit is arranged at the connection end between the full-bridge conversion module and the magnet load; the sampling unit is used to collect the current value and the voltage value of the magnet load; The controller unit is connected to the sampling unit and the full-bridge conversion module respectively; the controller unit is used to generate a driving signal for the switch tube according to the current value and the voltage value to control the opening and closing of the switch tube, so that the full-bridge circuit outputs the preset output.

6. The correction power supply device for collider beam feedback according to claim 5, characterized in that: The controller unit includes a PID controller and a PWM wave generator; The PID controller is used to generate the amplitude of the modulation wave of the PWM wave generator according to the current value and the voltage value; The PWM wave generator is used to generate the driving signal according to the amplitude of the modulation wave.

7. The correction power supply device for collider beam feedback according to claim 5, characterized in that: The sampling unit includes a voltage sampler, a current sampler and an A / D conversion module; The voltage sampler and the current sampler are both connected to the controller unit through the A / D conversion module.

8. The correction power supply device for collider beam feedback according to claim 7, characterized in that: The A / D conversion module is connected to the controller unit via the SPI protocol.

9. A control method for a correction power supply device for collider beam feedback, characterized in that: The control method is applied to the correction power supply device for collider beam feedback according to any one of claims 1 to 8, and the control method comprises: Get the actual DC output of the full-bridge circuit; Determine the on-time and off-time of each of the multiple switch tubes included in the full-bridge conversion module according to the difference between the actual direct current and the reference current; According to the number of the full-bridge circuits and the number of the multiple switch tubes included in the full-bridge conversion module, a carrier phase shifting technology is applied to determine the turn-on time and turn-off time of each of the multiple switch tubes; The driving signals of each of the multiple switch tubes are determined according to the on-time and the off-time as well as the on-time and the off-time, so that the full-bridge circuit outputs a preset output; wherein the driving signal includes a duty cycle and a phase shift angle; the duty cycle is determined according to the on-time and the off-time; and the phase shift angle is determined according to the on-time and the off-time.

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