Radio frequency circuit and electronic equipment

Abstract

The invention discloses a radio frequency circuit and electronic equipment. The radio frequency circuit comprises a processor, a radio frequency integrated circuit, a first power amplifier, a first coupler, a combiner and a first antenna, the processor is electrically connected with the radio frequency integrated circuit, the radio frequency integrated circuit comprises a first transmitting end, and the first transmitting end, the first power amplifier, the first coupler, the combiner and the first antenna are electrically connected in sequence; a first emission path is formed; the radio frequency integrated circuit is electrically connected with the coupling end of the first coupler, and the processor is used for detecting the output power of the coupling end of the first coupler based on the radio frequency integrated circuit to obtain a first power detection value; the radio frequency integrated circuit is electrically connected with the combiner, and the processor is used for detecting power information of the combiner based on the radio frequency integrated circuit to obtain a second power detection value; and the processor is used for adjusting the transmitting power of the first transmitting end according to the first power detection value and the second power detection value.

Description

Technical Field

[0001] The present application relates to the field of antenna technology, and in particular to a radio frequency circuit and electronic equipment. Background Art

[0002] In RF systems, the main purpose of RF power control is to adjust the power level of the output signal to meet the needs of different application scenarios. In related technologies, RF power is usually adjusted through a feedback loop. Specifically, the output power at a specific location in the RF system can be detected and the detected value can be compared with the preset target power. Then, the control circuit will adjust the gain of the amplifier or the attenuation level of the attenuator accordingly to make the output power reach the desired value. However, due to the complexity and diversity of RF working scenarios, the isolation of devices in different scenarios varies, and the impedance presented by the switch in different states is also different. Therefore, a set of calibration parameters may not be able to meet the power control of all scenarios, which may lead to poor accuracy of power control in some scenarios. Summary of the invention

[0003] The present application provides a radio frequency circuit and an electronic device, which can improve the accuracy of power control of the radio frequency circuit.

[0004] In a first aspect, the present application provides a radio frequency circuit, including a processor, a radio frequency integrated circuit, a first power amplifier, a first coupler, a combiner, and a first antenna, wherein the processor is electrically connected to the radio frequency integrated circuit, the radio frequency integrated circuit includes a first transmitting end, and the first transmitting end, the first power amplifier, the first coupler, the combiner, and the first antenna are electrically connected in sequence to form a first transmitting path;

[0005] The radio frequency integrated circuit is electrically connected to the coupling end of the first coupler, and the processor is used to detect the output power of the coupling end of the first coupler based on the radio frequency integrated circuit to obtain a first power detection value, wherein the first power detection value is used to characterize the power of the input end of the first coupler;

[0006] The radio frequency integrated circuit is electrically connected to the combiner, and the processor is used to detect power information of the combiner based on the radio frequency integrated circuit to obtain a second power detection value;

[0007] The processor is used to adjust the transmission power of the first transmitting end according to the first power detection value and the second power detection value.

[0008] In a second aspect, the present application provides an electronic device, comprising the radio frequency circuit described in the first aspect.

[0009] In an embodiment of the present application, in addition to detecting the output power of the coupling end of the first coupler based on the RF integrated circuit, the processor can also detect the power information of the combiner based on the RF integrated circuit, and adjust the transmission power of the first transmitting end based on the detected first power detection value and the second power detection value. Since the second power detection value can represent the actual power loss of the RF front end of the RF circuit, in the process of adjusting the transmission power of the first transmitting end, by considering the second power detection value, it is beneficial to avoid the problem of poor power control accuracy in some scenarios due to the different isolation levels of related devices in the RF front end in different scenarios, thereby helping to improve the accuracy of power control of the RF circuit. BRIEF DESCRIPTION OF THE DRAWINGS

[0010] Figure 1 This is one of the structural schematic diagrams of comparative scheme 1 of the embodiment of the present application;

[0011] Figure 2 This is the second structural schematic diagram of comparative scheme 1 of the embodiment of the present application;

[0012] Figure 3 This is a schematic diagram of the structure of Comparative Scheme 2 of the embodiment of the present application;

[0013] Figure 4 is Figure 3 Schematic diagram of simulation results obtained by simulation based on ;

[0014] Figure 5 This is one of the structural schematic diagrams of a radio frequency circuit provided in an embodiment of the present application;

[0015] Figure 6 is based on Figure 5 A schematic diagram of a process for power regulation of a radio frequency circuit;

[0016] Figure 7 is a relationship diagram corresponding to the relationship z=x-k0 in the embodiment of the present application;

[0017] Figure 8 is a schematic diagram of a three-dimensional coordinate system in an embodiment of the present application;

[0018] Fig. 9 is a schematic diagram of a two-dimensional projection coordinate system in an embodiment of the present application;

[0019] Fig.10 This is the second structural diagram of a radio frequency circuit provided in an embodiment of the present application;

[0020] Fig.11 yes Fig.10 A local enlarged view of the connection between the first transmission line and the microstrip coupler;

[0021] Fig.12 This is a third structural diagram of a radio frequency circuit provided in an embodiment of the present application;

[0022] Fig.13 This is a fourth structural diagram of a radio frequency circuit provided in an embodiment of the present application;

[0023] Fig.14 yes Fig.13 A partial enlarged view of the area between the processor and the RF integrated circuit. DETAILED DESCRIPTION

[0024] The following will be combined with the drawings in the embodiments of the present application to clearly describe the technical solutions in the embodiments of the present application. Obviously, the described embodiments are part of the embodiments of the present application, rather than all the embodiments. All other embodiments obtained by ordinary technicians in this field based on the embodiments in the present application belong to the scope of protection of this application.

[0025] The terms "first", "second", etc. in the specification and claims of the present application are used to distinguish similar objects, and are not used to describe a specific order or sequence. It should be understood that the data used in this way can be interchangeable under appropriate circumstances, so that the embodiments of the present application can be implemented in an order other than those illustrated or described here, and the objects distinguished by "first", "second", etc. are generally of one type, and the number of objects is not limited. For example, the first object can be one or more. In addition, "and / or" in the specification and claims represents at least one of the connected objects, and the character " / " generally indicates that the objects associated with each other are in an "or" relationship.

[0026] In the related art, the RF power control scheme is implemented by detecting the coupling loss (CPL), such as Figure 1 As shown in FIG. 1 , during the transmission (TX) signal process, it will pass through the radio frequency front-end (RFFE) modules such as the power amplifier (PA) and the transmitter module (TXM), and will also pass through the coupler (coupler), which can be an independent device or integrated in the TXM. The baseband processor 100 (BBP) Figure 2 The path indicated by the dotted arrow detects the signal size of the CPL to determine the real-time transmission power of the antenna, and adjusts the TX signal size of the RFIC as needed to complete the closed loop of power control.

[0027] Power delivery (PD) requires the RF link to be calibrated in advance, and information such as loss on the path is saved in the electronic device through calibration parameters to ensure power accuracy.

[0028] like Figure 2 As shown in the figure, assuming that the target power at point B of the antenna is 23dBm, and the CPL power detected by the BBP at point D is 0dBm, the calibration parameter coupler loss can be recorded as -23. In subsequent actual work, the power of the antenna port can be calculated by the BBP detection power and coupler loss to achieve power control. For example, when the antenna transmit power is 20dBm, the RFIC TX power needs to be adjusted until the BB detects -3dBm, that is, 20dBm-23dB.

[0029] Assuming that the insertion loss from the output point A of the PA to the antenna point B is 5dB, when B transmits 23dBm, the TX power at A is 28dBm, that is, 23dBm+5dB. Theoretically, the impedance of the section A→C→D is stable, that is, when the output point A of the PA transmits 28dBm, the BBP can detect 0dBm at point D.

[0030] Normally, when the RF front-end path is fixed, the insertion loss of A→B is also stable. However, as the architecture becomes more complex, the insertion loss of A→B will change with the change of working status. Assuming that the insertion loss of A→B changes from 5dB to 7dB, when A transmits 28dBm, D still detects 0dBm, that is, BBP thinks that the transmission at point B is still 23dBm, but in fact the power at point B is only 21dBm, that is, 28dBm-7dB. At this time, the power control is no longer accurate.

[0031] The root cause of this problem is that the insertion loss of the RF front end is no longer fixed due to the diversity of working scenarios, and is usually caused by the isolation of the combiner 500 or the switch. For example, please refer to the following scenario 1 and scenario 2:

[0032] Scenario 1:

[0033] Due to the deviation in the consistency of the performance of the combiner 500 (diplexer) monomer, even if they all meet the requirements of the specification, the specification range is very large. When the upper and lower limit device monomers are placed on the PCB board, the difference in the entire link will be further magnified. From the perspective of insertion loss alone, the difference in device monomers is within 0.4dB.

[0034] Scenario 2:

[0035] like Figure 3As shown in the figure, in the ENDC scenario, in addition to the original TX0, the TX1 path is also working. In this coexistence scenario, the three-pole three-throw (3P3T) will have different working states, which also leads to different impedances at both ends of the diplexer.

[0036] For example, see Figure 4 , select a set of diplexer and 3P3T, through simulation, it can be seen that when the impedance of point F of the diplexer is 50ohm, Figure 4 As can be seen from the blue line in the figure, the impedance position of E→G is relatively convergent at this time, and the insertion loss is relatively stable and normal. However, when the 3P3T switch connected to F is set to the isolation state, Figure 4 As can be seen from the red line in the figure, the insertion loss from E to G changes greatly. Affected by this, the insertion loss and impedance from A to B in the figure above will also change. Therefore, the original PD solution will fail in this scenario.

[0037] In the following, in conjunction with the accompanying drawings, a radio frequency circuit and an electronic device provided in an embodiment of the present application are described in detail through specific embodiments and their application scenarios.

[0038] See also Figure 5 , an embodiment of the present application provides a radio frequency circuit, the radio frequency circuit comprising a processor 100, a radio frequency integrated circuit 200, a first power amplifier 300, a first coupler 400, a combiner 500 and a first antenna 600, the processor 100 is electrically connected to the radio frequency integrated circuit 200, the radio frequency integrated circuit 200 comprises a first transmitting end 201, the first transmitting end 201, the first power amplifier 300, the first coupler 400, the combiner 500 and the first antenna 600 are electrically connected in sequence to form a first transmitting path;

[0039] The RFIC 200 is electrically connected to the coupling end 401 of the first coupler 400, and the processor 100 is used to detect the output power of the coupling end 401 of the first coupler 400 based on the RFIC 200 to obtain a first power detection value, wherein the first power detection value is used to characterize the power of the input end 402 of the first coupler 400;

[0040] The RFIC 200 is electrically connected to the combiner 500, and the processor 100 is used to detect power information of the combiner 500 based on the RFIC 200 to obtain a second power detection value;

[0041] The processor 100 is configured to adjust the transmit power of the first transmitting end 201 according to the first power detection value and the second power detection value.

[0042] The processor 100 may be various types of processors 100, for example, a BBP, or other processors 100 in an electronic device. The first antenna 600 may be used as various types of antennas in an electronic device. In addition, during the test process, the first antenna 600 may also be an antenna test socket, so that the actual transmission power of the antenna may be directly read based on the antenna test socket during the test process.

[0043] It is understandable that the RF circuit can send antenna signals based on the first transmission path. In the process of the RF circuit sending antenna signals based on the first transmission path, the processor 100 is used to adjust the transmission power of the first transmitting end 201 according to the first power detection value and the second power detection value.

[0044] In the above-mentioned first transmitting path, the input end 402 of the first coupler 400 is electrically connected to the output end of the first power amplifier 300, wherein the signal power of the input end 402 of the first coupler 400 is associated with the signal power of the coupling end 401 of the first coupler 400, for example, in some types of couplers, the signal power of its input end is positively correlated with the signal power of the coupling end. Based on this, the signal power of the input end 402 of the first coupler 400 can be determined according to the signal power of the coupling end 401 of the first coupler 400, and the signal transmission power of the first transmitting end 201 can be directly obtained, therefore, according to the signal transmission power of the first transmitting end 201 and the signal power of the input end 402 of the first coupler 400, the power loss between the first transmitting end 201 and the first coupler 400 is determined, that is, the signal power of the coupling end 401 of the first coupler 400 can represent the power loss between the first transmitting end 201 and the first coupler 400, wherein the above-mentioned first power detection value can be the signal power of the coupling end 401 of the first coupler 400.

[0045] In some embodiments of the present application, the second power detection value can be used to characterize the power loss in the combiner 500. In other embodiments of the present application, the second power detection value can be used to characterize the power of the output end 503 of the combiner 500. It can be understood that when the insertion loss of the RF front end changes due to the change in the isolation of the switch components of the combiner 500 or other components in the RF circuit, the second power detection value will also change accordingly. Therefore, the actual power loss of the RF front end of the RF circuit can be determined based on the second power detection value. In this way, in the process of adjusting the transmission power of the first transmitting end 201, by considering the second power detection value, it is helpful to avoid the problem of poor accuracy of power control in some scenarios due to the different isolations of the related components in the RF front end in different scenarios.

[0046] In some embodiments of the present application, the process in which the processor 100 adjusts the transmit power of the first transmitting end 201 according to the first power detection value and the second power detection value may specifically include the following process: the sizes of the first power detection value and the second power detection value corresponding to the RF circuit in various scenarios can be predetermined, and the power adjustment parameters corresponding to the various scenarios can be predetermined. In this way, in the subsequent power adjustment process, the current scenario of the RF circuit can be determined according to the first power detection value and the second power detection value, and the corresponding power adjustment parameters can be called based on the determined scenario to adjust the transmit power of the first transmitting end 201.

[0047] In other embodiments of the present application, the process in which the processor 100 adjusts the transmit power of the first transmitting end 201 according to the first power detection value and the second power detection value may specifically include the following process: the processor 100 may pre-determine the difference between the first power detection value and the second power detection value under a specific reference state, and the actual transmit power of the first antenna 600, and determine the correlation between the difference and the actual transmit power based on this, so that the actual transmit power of the first antenna 600 can be determined according to the correlation based on the difference between the first power detection value and the second power detection value, and the transmit power of the first transmitting end 201 can be adjusted based on the relationship between the actual transmit power and the expected transmit power.

[0048] In this implementation, in addition to detecting the output power of the coupling end 401 of the first coupler 400 based on the RF integrated circuit 200, the processor 100 can also detect the power information of the combiner 500 based on the RF integrated circuit 200, and adjust the transmission power of the first transmitting end 201 based on the detected first power detection value and the second power detection value. Since the second power detection value can represent the actual power loss of the RF front end of the RF circuit, in the process of adjusting the transmission power of the first transmitting end 201, by considering the second power detection value, it is beneficial to avoid the problem of poor power control accuracy in some scenarios due to the different isolation levels of related devices in the RF front end in different scenarios, thereby helping to improve the accuracy of power control of the RF circuit.

[0049] Optionally, see Figure 5 , the RF circuit further includes a second power amplifier 700, a second coupler 800, a first switch element 900, a second antenna 1100 and a third antenna 1200, the RF integrated circuit 200 further includes a first coupling terminal 202, a second transmitting terminal 204 and a second coupling terminal 205, the first switch element 900 includes a first connection terminal 901, a second connection terminal 902, a third connection terminal 903 and a fourth connection terminal 904;

[0050] The RFIC 200 is electrically connected to the coupling end 401 of the first coupler 400 via the first coupling end 202, the combiner 500 includes a first input end and a second input end, and the output end of the first coupler 400 is electrically connected to the first input end 501 of the combiner 500;

[0051] The second transmitting end 204, the second power amplifier 700, the second coupler 800 and the first connecting end 901 are electrically connected in sequence, the second connecting end 902 is electrically connected to the second antenna 1100, the third connecting end 903 is electrically connected to the third antenna 1200, the fourth connecting end 904 is electrically connected to the second input end 502 of the combiner 500, and the RF integrated circuit 200 is electrically connected to the coupling end 801 of the second coupler 800 via the second coupling end 205;

[0052] The second power detection value is a power value leaked from the first input terminal 501 of the combiner 500 to the second input terminal 502 of the combiner 500 .

[0053] The second antenna 1100 and the third antenna 1200 can be used as various types of antennas in electronic devices, and the second antenna 1100 and the third antenna 1200 are other antennas besides the first antenna 600. In addition, during the test process, the second antenna 1100 and the third antenna 1200 can also be antenna test sockets. At this time, the first antenna 600, the second antenna 1100 and the third antenna 1200 are three different antenna test sockets. In this way, the actual transmission power of the antenna can be directly read based on the antenna test socket during the test process.

[0054] The first switch element 900 can be any type of switch element, see Figure 5 In some embodiments of the present application, the first switch element 900 is a 3P3T switch. The radio frequency circuit also includes a first receiving module 1300 (LFEM1) and a second receiving module 1400 (LFEM2). The radio frequency integrated circuit 200 also includes a first coupling terminal 202, a first receiving terminal 203, a second transmitting terminal 204, a second coupling terminal 205, and a second receiving terminal 206. The first switch element 900 also includes a fifth connection terminal 905 and a sixth connection terminal 906. The fifth connection terminal 905 is electrically connected to the first receiving terminal 203 through the first receiving module 1300, and the sixth connection terminal 906 is electrically connected to the second receiving terminal 206 through the second receiving module 1400.

[0055] See also Figure 5 In the above embodiment, the electrical connection between the RF integrated circuit 200 and the combiner 500 may refer to: the second coupling end 205 of the RF integrated circuit 200 is electrically connected to the second input end 502 of the combiner 500 through the second coupler 800 and the first switch element 900 in sequence.

[0056] See also Figure 5 , the electrical connection between the processor 100 and the RF integrated circuit 200 may include: there is a communication link between each receiving end of the RF integrated circuit 200 and the processor 100, there is a communication link between each transmitting end of the RF integrated circuit 200 and the processor 100, there is a communication link between each coupling end of the RF integrated circuit 200 and the processor 100, and the processor 100 and the RF integrated circuit 200 can transmit in-phase / Quadrature (IQ) signals through the communication link.

[0057] Please see further Figure 5In the process of transmitting a signal based on the first transmitting path, the first input end 501 of the combiner 500 is used as the signal receiving end of the combiner 500 to receive the signal output by the first coupler 400. The second input end 502 of the combiner 500 can be an idle input end of the combiner 500. Since part of the power will leak to the second input end 502 of the combiner 500 during the process of receiving the signal based on the first input end of the combiner 500, and the first switch 900 is in different working states, the power leaked from the first input end 501 of the combiner 500 to the second input end 502 of the combiner 500 is also different, and the power leaked to the second input end can be along Figure 5 The path indicated by the dotted arrow is transmitted from the second input terminal 502 of the combiner 500 to the second coupling terminal 205 of the RF integrated circuit 200 to detect the power information of the combiner 500 .

[0058] In this implementation, the electrical connection between the second coupling end 205 of the RF integrated circuit 200 and the second input end 502 of the combiner 500 is established by reusing the existing devices in the RF circuit, which is conducive to reducing the cost of the RF circuit and reducing the complexity of the RF circuit structure, that is, the detection of the power information of the combiner 500 can be achieved without increasing the cost and structural complexity of the RF circuit. And by detecting the leakage power of the second input end 502 of the combiner 500, the working scene of the RF circuit can be determined according to the size of the leakage power, which is conducive to calling the corresponding power adjustment parameters based on the determined working scene to adjust the transmission power of the first transmitting end 201, avoiding the basic RF performance problems caused by the change of impedance insertion loss due to different working states of the RF front end.

[0059] Optionally, the radio frequency circuit includes N working states, where N is an integer greater than 1, and in the N working states, power differences in different working states are different, and the power difference is: a difference between the first power detection value and the second power detection value detected in the corresponding working state;

[0060] The N working states correspond one-to-one to N groups of calibration parameters, and the processor 100 is used to determine the target working state according to the difference between the first power detection value and the second power detection value, and the processor 100 is also used to adjust the transmission power of the first transmitting end 201 according to the calibration parameters corresponding to the target working state, wherein the target working state is a working state among the N working states.

[0061] The above-mentioned N working states may include all working states that the RF circuit may include. For example, when the RF circuit includes a double-pole double-throw switch (DPDT), the RF circuit has two working states; when the RF circuit includes a 3P3T, the RF circuit has six working states; when the RF circuit includes a 4P4T, the RF circuit has 24 working states. The calibration parameters corresponding to various working states can be determined in advance in the test phase. In this way, the working state of the RF circuit can be determined based on the first power detection value and the second power detection value, and the calibration parameters corresponding to the working state of the RF circuit can be called to adjust the transmission power of the first transmitting end 201.

[0062] See also Figure 5 , because the leakage power in the second input terminal 502 of the combiner 500 is different in different working states of 3P3T, and the impedance of the RF path is fixed in a fixed working state, at this time, regardless of the transmission power, the difference between the first power detection value and the second power detection value is the same. And because the impedance of the RF path is different in different working states, the difference corresponding to different working states in N kinds of working states may be different, wherein the difference is the difference between the first power detection value and the second power detection value detected in the corresponding working state.

[0063] For example, if in the first working state, the transmission power of point A is 28dBm, when 3P3T is in working state 1, the first power detection value is 0dBm, the second power detection value is -40dBm, the difference between the first power detection value and the second power detection value should be constant at 40dB, and the difference is constant in working state 1. In the second working state, 3P3T is in working state 2, the first power detection value is 0dBm, and the second power detection value is -50dBm. At this time, the difference between the two is 50dB. In this way, after the first power detection value and the second power detection value are detected, if the difference between the first power detection value and the second power detection value is 40dB, the calibration parameters corresponding to the first working state can be called to adjust the transmission power of the first transmitting end 201. After the first power detection value and the second power detection value are detected, if the difference between the first power detection value and the second power detection value is 50dB, the calibration parameters corresponding to the second working state can be called to adjust the transmission power of the first transmitting end 201.

[0064] The calibration parameter may be a pre-set power adjustment parameter, for example, a power compensation value. In addition, the calibration parameter may also be a coupler loss parameter in the following embodiments.

[0065] See also Figure 6, which is a method proposed in the embodiment of the present application. Figure 5 The power regulation method corresponding to the RF circuit shown in the figure is a flow chart, wherein the power regulation method comprises the following steps:

[0066] Pre-save the calibration parameters corresponding to N working states;

[0067] Calculate the difference between the detection results of the two PDs under different working states, and store the difference in association with the corresponding calibration parameters, wherein the detection results of the two PDs include: the first power detection value obtained by the RF integrated circuit 200 detecting the output power of the coupling end 401 of the first coupler 400, and the second power detection value obtained by the RF integrated circuit 200 detecting the power information of the combiner 500;

[0068] During the power adjustment process, the difference between the detection results of the two PDs when the RF circuit is working can be obtained;

[0069] The current working state is determined according to the difference between the detection results of the two PDs, and the calibration parameters corresponding to the current working state are called to adjust the transmission power of the first transmitting end 201.

[0070] In this implementation, by predetermining N working states included in the RF circuit and the calibration parameters corresponding to each working state, in the subsequent power adjustment process, the target working state can be determined according to the difference between the first power detection value and the second power detection value, and the transmission power of the first transmitting end 201 can be adjusted according to the calibration parameters corresponding to the target working state. Since the RF circuit is in different working states, the transmission power of the first transmitting end 201 can be adjusted using the calibration parameters corresponding to the corresponding working states, which is beneficial to improving the accuracy of power adjustment of the RF circuit.

[0071] Because based on Figure 5 The adjustment accuracy of the power regulation in the illustrated embodiment is not easy to define, and the recognition ability for complex working scenarios is limited, and there is no way to unify the standards. For example, the switch that affects the impedance change connected to the combiner 500 may be DPDT, 3P3T, or even 4P4T. As the device becomes more complex, the number of scenarios will also increase exponentially. DPDT has two states, 3P3T has six states, and 4P4T has 24 states. Moreover, increasing the judgment of logic may affect the response time of the system and cause unnecessary jamming. Based on this, the power regulation process for such complex scenarios is explained below with other embodiments:

[0072] Optionally, the output power z of the first antenna 600 and the first power detection value x satisfy the following relationship: z=x-k0+(k0-k1), wherein k0 is a coupling loss parameter of the radio frequency circuit in a reference working state, and k1 is used to characterize an actual coupling degree between the output power of the first antenna 600 and the first power detection value;

[0073] The processor 100 is used to determine the value of (k0-k1) in a first calibration curve in a preset three-dimensional coordinate system according to the first power detection value and the second power detection value, wherein three coordinate axes of the three-dimensional coordinate system include: a first coordinate axis for representing the first power detection value, a second coordinate axis for representing the second power detection value, and a third coordinate axis for representing the value of (k0-k1); the first calibration curve is used to represent: the relationship between the first power detection value, the second power detection value and the value of (k0-k1);

[0074] The processor 100 is further configured to determine the output power z of the first antenna 600 based on the relationship using the value of (k0-k1), and to adjust the transmission power of the first transmitting end 201 according to the determined output power z of the first antenna 600.

[0075] The conventional power control scheme is linear. The relationship between ANT power and PD is as follows: Figure 7 :

[0076] ANT power = PD-coupler loss

[0077] This relationship can be simply described as z=x-k0, where k0 is the coupler loss, which is obtained through calibration and is a fixed constant. ANT power is the actual transmission power of the first antenna 600, and PD is the first power detection value obtained by the RF integrated circuit 200 detecting the output power of the coupling end 401 of the first coupler 400. Z is ANT power, and x is PD.

[0078] In the embodiment of the present application, the joint power control scheme uses the main power detection PD1 and the auxiliary power detection PD2 to jointly map and correct k0 (coupler loss). The parameters required for actual work are shown in Table 1 below, which lists eight random working states:

[0079] Table 1:

[0080]

[0081] The explanations of the relevant definitions in Table 1 are as follows: the test socket power (ANT power) is the actual transmission power of the first antenna 600; PD1 is the result of the main path power detection, that is, PD1 is the first power detection value; coupler loss0 is the coupling degree between the output power of the first antenna 600 and the first power detection value when the RF circuit is in working state 1 (state1), wherein the coupler loss0 is a coupling degree parameter set in the test process, and its value can be calculated by the above formula (ANTpower=PD-coupler loss). Specifically, in the test process, after the RF circuit is controlled to enter state1, a signal can be transmitted based on the above first RF path, and then the actual transmission power ANTpower of the first antenna 600 can be directly read based on the antenna test socket used to characterize the first antenna 600. At the same time, based on the RF integrated circuit 200, the output power PD of the coupling end 401 of the first coupler 400 is detected, and the read ANTpower and the detected PD are substituted into the above formula to obtain the value of the coupler loss at this time, and the value of the coupler loss at this time can be set to the above k0.

[0082] It can be understood that the value of the above k1 can also be calculated according to the method of calculating k0 mentioned above. For example, for the relevant parameters of State2, during the test process, after the RF circuit is controlled to enter state2, a signal can be transmitted based on the above first RF path, and then the actual transmission power ANTpower of the first antenna 600 can be directly read based on the antenna test socket used to characterize the first antenna 600. At the same time, the output power PD of the coupling end 401 of the first coupler 400 is detected based on the RF integrated circuit 200. The read ANTpower and the detected PD are substituted into the above formula to obtain the value of k1 at this time. At the same time, the value of k0 is still the value of k0 calculated in state1. At this time, by substituting (k0-k1), the correction value corresponding to state1 can be obtained.

[0083] Similarly, the calculation process of the actual coupling degree between the output power of the first antenna 600 and the second power detection value k2 is similar to the calculation process of k1, ensuring that the value of PD in the above formula is replaced by the power information of the combiner 500 detected by the RF integrated circuit 200.

[0084] Since ANTpower and PD in the above formula will change with the working state and transmission power of the RF circuit under different working states, and in a specific working mode, the value of coupler loss remains unchanged, and the values ​​of coupler loss corresponding to different working modes are usually different. Therefore, state1 can be used as a reference working state. The difference between other working states and state1 mainly lies in the need to correct the value of k0 in the above formula. Based on this, the above formula can be rewritten as: z = x-k0 + (k0-k1), where (k0-k1) is the corrected value of k0, and (k0-k1) is referred to as: CPLcomp. It can be understood that when the RF circuit is in state1, k0 = k1. Since in the actual adjustment process, the above-mentioned PD1 and PD2 can be directly detected, and the value of k0 can be predetermined, therefore, it is only necessary to calculate (k0-k1) to obtain the real-time transmission power z of the first antenna 600, and the transmission power of the first transmitting end 201 can be adjusted according to the relative size of the expected transmission power of the first antenna 600 and z. For example, when the expected transmission power of the first antenna 600 is 25dBm and the value of z is 24dBm, the transmission power of the first transmitting end 201 can be controlled to increase by 1dBm, and then the relative size of the expected transmission power of the first antenna 600 and z is detected again until the expected transmission power of the first antenna 600 is equal to z. For another example, when the expected transmission power of the first antenna 600 is 25dBm and the value of z is 26dBm, the transmission power of the first transmitting end 201 can be controlled to be reduced by 1dBm, and then the relative size of the expected transmission power of the first antenna 600 and z is detected again until the expected transmission power of the first antenna 600 is equal to z.

[0085] It can be seen that in the process of power regulation of the RF circuit, if (k0-k1) can be calculated based on the detected PD1 and PD2, relatively accurate power regulation of the RF circuit can be achieved, and the data of the 8 states in the above Table 1 can be obtained by randomly selecting 8 states of the RF circuit during the test process, and calculating by reading the value of the antenna test socket and the first power detection value and the second working detection value. Therefore, the above three-dimensional coordinate system can be established with PD1 as the first coordinate axis, PD2 as the second coordinate axis, and the value of (k0-k1) as the third coordinate axis, and the coordinate points of the 8 coordinate values ​​(PD1, PD2, (k0-k1)) corresponding to the 8 states in the above Table 1 are determined in the established three-dimensional coordinate system, and then the above first calibration curve can be obtained by smoothly connecting the 8 coordinate points, as shown in FIG. Figure 8 Shown is a schematic diagram of the three-dimensional coordinate system.

[0086] The above-mentioned determination of the value of (k0-k1) in the first calibration curve in the preset three-dimensional coordinate system according to the first power detection value PD1 and the second power detection value PD2 may refer to: taking PD1 and PD2 as matching conditions, determining the point in the first calibration curve where the first power detection value and the second power detection value are closest to "PD1 and PD2", and taking the value of the third coordinate axis of the point as the value of (k0-k1) at this time. Then, using the value of (k0-k1), the output power z of the first antenna 600 is determined based on the relationship, and is used to adjust the transmission power of the first transmitting end 201 according to the determined output power z of the first antenna 600.

[0087] In this implementation, a three-dimensional coordinate system is established, and a first calibration curve is determined in the three-dimensional coordinate system. In this way, the subsequent first power detection value and the second power detection value detected in real time can be used to determine the value of (k0-k1) at this time in the three-dimensional coordinate system, so that the real-time transmission power of the first antenna 600 can be calculated based on the determined (k0-k1). In this way, it is only necessary to compare the real-time transmission power of the first antenna 600 with the expected transmission power to determine the adjustment amount of the transmission power of the first transmitting end 201, and adjust the transmission power of the first transmitting end 201 based on the determined adjustment amount. In this way, no matter how many states the RF circuit exists in, the transmission power of the first transmitting end 201 can be adjusted relatively accurately, which is conducive to realizing the power adjustment process in complex scenarios.

[0088] Optionally, the processor 100 is used to determine a first coordinate point in a second calibration curve in a two-dimensional projection coordinate system according to the first power detection value and the second power detection value, wherein the two-dimensional projection coordinate system is a coordinate system composed of the first coordinate axis and the second coordinate axis, the second calibration curve is a curve obtained by projecting the first calibration curve onto the two-dimensional projection coordinate system, the first coordinate point is a position point in the second calibration curve that is closest to the second coordinate point, and the second coordinate point is a coordinate position point corresponding to the first power detection value and the second power detection value in the two-dimensional projection coordinate system;

[0089] The processor 100 is further configured to determine a third coordinate point corresponding to the first coordinate point in the first calibration curve, and the processor 100 is further configured to determine a coordinate value corresponding to the third coordinate point in the third coordinate axis as the value of (k0-k1).

[0090] See also Fig. 9 , is the above two-dimensional projection coordinate system, which can be Figure 8The three-dimensional coordinate system shown is projected onto the coordinate system composed of the first coordinate axis and the second coordinate axis to obtain a two-dimensional projection coordinate system. Accordingly, the second calibration curve is a curve obtained by projecting the first calibration curve onto the two-dimensional projection coordinate system. Since the second calibration curve is a projection curve of the first calibration curve, each point in the first calibration curve has a corresponding projection point in the second calibration curve, and the points in the first calibration curve have the same x and y coordinate values ​​as the corresponding projection points.

[0091] Specifically, in the process of power regulation, the values ​​of PD1 and PD2 can be obtained by detection first, and the second coordinate point (PD1, PD2) can be determined in the two-dimensional projection coordinate system. Then, the first coordinate point closest to the second coordinate point can be determined in the second calibration curve. Since the points in the second calibration curve are used as projection points of the first calibration curve, the third coordinate point corresponding to the first coordinate point can be determined in the first calibration curve according to the determined first coordinate point, and the coordinate value of the third coordinate point on the third coordinate axis can be directly read from the three-dimensional coordinate system, and the coordinate value of the read third coordinate point on the third coordinate axis is determined as the value of (k0-k1), thereby realizing the determination process of the value of (k0-k1).

[0092] In this embodiment, by establishing a two-dimensional projection coordinate system corresponding to the three-dimensional coordinate system, the second coordinate point can be determined in the two-dimensional projection coordinate system directly based on the first power detection value and the second power detection value obtained by detection, and by determining the coordinate point in the second calibration curve that is closest to the second coordinate point as the first coordinate point, and the coordinate point in the first calibration curve corresponding to the first coordinate point as the third coordinate point, and determining the coordinate value of the third coordinate point on the third coordinate axis as the value of (k0-k1), thereby realizing the process of determining the value of (k0-k1) in the first calibration curve in the preset three-dimensional coordinate system according to the first power detection value and the second power detection value.

[0093] In the above embodiments, the optimization is mainly performed on the basis of the original circuit by adjusting the calibration and power control algorithm, and the implementation method is relatively complicated. In addition, the demodulation capability of the PD by the radio frequency integrated circuit 200 is required to be high. Based on this, other embodiments are provided below. The embodiments below mainly solve the problem of inaccurate power control by hardware, and at the same time, the demodulation capability of the current conventional radio frequency transceiver can be ensured.

[0094] Optionally, see Fig.10 , the radio frequency circuit further includes a microstrip coupler 1600, and the output end 503 of the combiner 500 is electrically connected to the first antenna 600 through a first transmission line 1500;

[0095] The RFIC 200 is electrically connected to the output end 503 of the combiner 500 through the microstrip coupler 1600 and the first transmission line 1500 in sequence, wherein the microstrip coupler 1600 is coupled to the first transmission line 1500 .

[0096] See also Fig.10 ,exist Fig.10 In the illustrated embodiment, the radio frequency circuit also includes a combiner 500. As described in the above embodiment, the impedance R connected to the second input terminal 502 of the combiner 500 has a great influence on the insertion loss of the main path.

[0097] In this embodiment, a microstrip coupler 1600 is added between the combiner 500 and the first antenna 600, and the coupling end of the microstrip coupler 1600 and the coupling degree of the coupler on the original main path are connected to the RF integrated circuit 200. This is equivalent to having a PD before and after the combiner 500. As mentioned above, the root cause of the change in path insertion loss is the change in the impedance of the combiner 500. Here, we mainly focus on two aspects: one is whether the power before and after the impedance change is accurate, and the other is the reliability of the device after the impedance change.

[0098] The implementation form of the microstrip coupler 1600 is as follows: Fig.11 , at the adjacent layer projection position of the TRX microstrip line on the surface of the PCB, three staggered strip lines that overlap with its projection part are added, one end of the strip line is connected to a 50ohm resistor as an isolation end, and the other end is connected to the RF integrated circuit 200. According to different operating frequencies, the width of the strip line or the projection overlap length can be fine-tuned to achieve the desired coupling degree. Among them, the TRX microstrip is the above-mentioned first transmission line 1500, the microstrip coupler 1600 includes the strip line, and the strip line forms the coupling part of the microstrip coupler 1600, and the coupling part of the microstrip coupler 1600 is coupled with the first transmission line 1500.

[0099] Fig.12 In the embodiment shown, the principle of power regulation can be: the original power detection PD1 mainly realizes the control of PA reliability to avoid over-power generation and PA burning, because the impedance from PA to the coupler is almost unchanged. The newly added microstrip coupler 1600PD2 mainly realizes the power accuracy of the test socket, because the impedance between the microstrip coupler 1600 and the test socket is also stable.

[0100] For example, see Fig.12, PA sends out 28dBm (A), PD1 detects 1dBm (D), power before combiner 500 is 25dBm (E), power after combiner 500 is 24dBm (F), antenna test socket power is 23dBm (B), and PD2 detects -5dBm. If there is no impedance change, the difference between PD1 and PD2 is fixed at 6dB.

[0101] If the impedance of the second input end 502 of the combiner 500 changes, resulting in a 0.5 dB decrease in insertion loss, the power after the combiner 500 increases to 24.5 dBm (F), the power of the antenna test socket increases to 23.5 dBm (B), and the detection power of PD2 increases to -4.5 dBm. The difference between PD1 and PD2 decreases to 5.5 dB. At this time, the value of PD1 can be adjusted down by 0.5 dB to keep the power of the antenna test socket at 23 dBm.

[0102] The same applies to scenarios where the insertion loss increases. However, it should be noted that in addition to achieving precise power control, attention should also be paid to PA reliability when the insertion loss increases. That is, PD1 cannot be too high to cause PA over-issuance. This can be solved by limiting PD1.

[0103] In this implementation, compared with the above-mentioned embodiment, the demodulation capability is not limited, the magnitude of PD2 is at the same level as PD1, and there will be no situation where the power of PD2 is too small, and some chips have insufficient demodulation capabilities, resulting in the power not being measured. In addition, the embodiment of the present application does not need to calibrate the parameters in multiple scenarios, but only needs to adjust PD1 according to the difference between PD1 and PD2 during actual operation. The calibration scheme is closest to the current one, and both the calibration time and efficiency can be guaranteed. At the same time, in terms of cost, the microstrip coupler 1600 is built through circuit routing, and the SP4T port of most RF architecture CPLs is also idle, which can be basically ignored.

[0104] Optionally, see Fig.10 , the RF circuit further includes a second switch element 1700, the RF integrated circuit 200 includes a first coupling end 202, the first coupling end 202 is electrically connected to the coupling end 401 of the first coupler 400 through the second switch element 1700, and the first coupling end 202 is also electrically connected to the output end of the microstrip coupler 1600 through the second switch element 1700;

[0105] When the second switch element 1700 is in the first state, the first coupling end 202 is connected to the coupling end 401 of the first coupler 400, and the first coupling end 202 is disconnected from the output end of the microstrip coupler 1600;

[0106] When the second switch element 1700 is in the second state, the first coupling end 202 is disconnected from the coupling end 401 of the first coupler 400 , and the first coupling end 202 is connected to the output end of the microstrip coupler 1600 .

[0107] The second switch 1700 may be a switch of various types, for example, SPDT or SP4T. In the process of power regulation, the working state of the second switch 1700 may be controlled to perform time-sharing detection on PD1 and PD2. For example, the second switch 1700 may be controlled to enter the first state first, and PD1 may be detected. After the detection of PD1 is completed, the second switch 1700 may be controlled to enter the second state, and then PD2 may be detected, so that time-sharing detection of PD1 and PD2 may be achieved.

[0108] In this embodiment, the coupling end of the microstrip coupler 1600 and the coupling end of the coupler on the original main path are connected to the CPL port of the RF integrated circuit 200 through the second switch element 1700. In this way, the two PDs only need to occupy one CPL port of the RF integrated circuit 200, which is beneficial for power regulation scenarios where the RF integrated circuit 200 can only provide one CPL port.

[0109] Optionally, see Fig.13 The RF integrated circuit 200 includes a first coupling end 202, a second coupling end 205, a first signal output end 207 and a second signal output end 208, wherein the first signal output end 207 is a signal output end corresponding to the first coupling end 202, and the second signal output end 208 is a signal output end corresponding to the second coupling end 205, the first coupling end 202 is electrically connected to the coupling end 401 of the first coupler 400, and the second coupling end 205 is electrically connected to the output end of the microstrip coupler 1600;

[0110] The radio frequency circuit further includes a subtractor 1800, the processor 100 includes a first detection terminal 101, the first signal output terminal 207 is electrically connected to the first input terminal 1801 of the subtractor 1800, the second signal output terminal 208 is electrically connected to the second input terminal 1802 of the subtractor 1800, and the output terminal 1803 of the subtractor 1800 is electrically connected to the first detection terminal 101;

[0111] The processor 100 is used to adjust the transmission power of the first transmitting end 201 according to the output result of the subtractor 1800.

[0112] Fig.13The illustrated embodiment is an embodiment of realizing precise power control by adding peripheral circuits based on the dual CPL radio frequency integrated circuit 200.

[0113] It should be noted that Fig.13 The power regulation principle in the embodiment shown is similar to Fig.10 The embodiments shown are similar, except that: Fig.13 In the illustrated embodiment, the output result of the subtractor 1800 is the difference between PD1 and PD2. Thus, during the power adjustment process, it is only necessary to compare the output result of the subtractor 1800 with the reference PD difference in the default scenario, and adjust the transmission power of the first transmitting end 201 according to the difference, thereby realizing the power adjustment process of the first transmitting end 201.

[0114] In this implementation, the power regulation process of the dual CPL RF integrated circuit 200 can be implemented, and by connecting the subtractor 1800 between the processor 100 and the RF integrated circuit 200, the result of the subtractor 1800 can be directly compared with the reference PD difference, thereby realizing the power regulation process of the first transmitting end 201, which is conducive to further simplifying the internal processing process of the processor 100 during the power regulation process.

[0115] Optionally, see Fig.13 and Fig.14 , the processor 100 further includes a second detection terminal 102, and the radio frequency circuit further includes a third switch element 1900, a fourth switch element 2200 and a fifth switch element 2100;

[0116] The first signal output terminal 207 is electrically connected to the input terminal 1901 of the third switch element 1900, the first output terminal 1903 of the third switch element 1900 is electrically connected to the first input terminal 1801 of the subtractor 1800, the output terminal 1803 of the subtractor 1800 is electrically connected to the first input terminal 2202 of the fourth switch element 2200, the second output terminal 1902 of the third switch element 1900 is electrically connected to the second input terminal 2201 of the fourth switch element 2200, and the output terminal 2203 of the fourth switch element 2200 is electrically connected to the first detection terminal 101;

[0117] The second signal output terminal 208 is electrically connected to the input terminal 2101 of the fifth switch element 2100 , the first output terminal 2102 of the fifth switch element 2100 is electrically connected to the second input terminal 1802 of the subtractor 1800 , and the second output terminal 2103 of the fifth switch element 2100 is electrically connected to the second detection terminal 102 .

[0118] The third switch element 1900 , the fourth switch element 2200 and the fifth switch element 2100 may all be single-pole double-throw switches.

[0119] It can be understood that, in the RF integrated circuit 200, in addition to the power regulation process requiring the output result of the subtractor 1800, the output results of CPL0 and CPL1 may also be required in other processes. Therefore, by adding the above-mentioned third switch element 1900, fourth switch element 2200 and fifth switch element 2100, the processor 100 can selectively obtain the first power detection value, the second power detection value and the difference between the two from the RF integrated circuit 200 by simply controlling the switching states of the third switch element 1900, the fourth switch element 2200 and the fifth switch element 2100.

[0120] In this embodiment, a third switch element 1900, a fourth switch element 2200 and a fifth switch element 2100 are added between the processor 100 and the RF integrated circuit 200. Thus, the processor 100 can selectively obtain the first power detection value, the second power detection value and the difference between the first power detection value, the second power detection value and the difference between the first power detection value, and the second power detection value.

[0121] An embodiment of the present application further provides an electronic device, which includes the radio frequency circuit described in the above embodiment.

[0122] In this implementation, since the electronic device includes the radio frequency circuit described in the above embodiment, the electronic device can implement each process of the radio frequency circuit in the above embodiment and has the same beneficial effects, which will not be described again to avoid repetition.

[0123] The embodiments of the present application are described above in conjunction with the accompanying drawings, but the present application is not limited to the above-mentioned specific implementation methods. The above-mentioned specific implementation methods are merely illustrative and not restrictive. Under the guidance of the present application, ordinary technicians in this field can also make many forms without departing from the purpose of the present application and the scope of protection of the claims, all of which are within the protection of the present application.

Claims

1. A radio frequency circuit, characterized in that: The device comprises a processor, a radio frequency integrated circuit, a first power amplifier, a first coupler, a combiner and a first antenna, wherein the processor is electrically connected to the radio frequency integrated circuit, the radio frequency integrated circuit comprises a first transmitting end, and the first transmitting end, the first power amplifier, the first coupler, the combiner and the first antenna are electrically connected in sequence to form a first transmitting path; The radio frequency integrated circuit is electrically connected to the coupling end of the first coupler, and the processor is used to detect the output power of the coupling end of the first coupler based on the radio frequency integrated circuit to obtain a first power detection value, wherein the first power detection value is used to characterize the power of the input end of the first coupler; The radio frequency integrated circuit is electrically connected to the combiner, and the processor is used to detect power information of the combiner based on the radio frequency integrated circuit to obtain a second power detection value; The processor is used to adjust the transmission power of the first transmitting end according to the first power detection value and the second power detection value.

2. The radio frequency circuit according to claim 1, characterized in that: The radio frequency circuit further includes a second power amplifier, a second coupler, a first switch element, a second antenna and a third antenna, the radio frequency integrated circuit further includes a first coupling end, a second transmitting end and a second coupling end, and the first switch element includes a first connecting end, a second connecting end, a third connecting end and a fourth connecting end; The RF integrated circuit is electrically connected to the coupling end of the first coupler through the first coupling end, the combiner includes a first input end and a second input end, and the output end of the first coupler is electrically connected to the first input end of the combiner; The second transmitting end, the second power amplifier, the second coupler and the first connecting end are electrically connected in sequence, the second connecting end is electrically connected to the second antenna, the third connecting end is electrically connected to the third antenna, the fourth connecting end is electrically connected to the second input end of the combiner, and the radio frequency integrated circuit is electrically connected to the coupling end of the second coupler through the second coupling end; The second power detection value is a power value leaked from the first input end of the combiner to the second input end of the combiner.

3. The radio frequency circuit according to claim 2, characterized in that: The radio frequency circuit includes N working states, where N is an integer greater than 1, and in the N working states, power difference values ​​under different working states are different, and the power difference value is: the difference between the first power detection value and the second power detection value detected in the corresponding working state; The N working states correspond one-to-one to N groups of calibration parameters, and the processor is used to determine the target working state according to the difference between the first power detection value and the second power detection value, and the processor is also used to adjust the transmission power of the first transmitting end according to the calibration parameters corresponding to the target working state, wherein the target working state is a working state among the N working states.

4. The radio frequency circuit according to claim 2, characterized in that: The output power z of the first antenna and the first power detection value x satisfy the following relationship: z=x-k0+(k0-k1), wherein k0 is a coupling loss parameter of the radio frequency circuit in a reference working state, and k1 is used to characterize the actual coupling degree between the output power of the first antenna and the first power detection value; The processor is used to determine the value of (k0-k1) in a first calibration curve in a preset three-dimensional coordinate system according to the first power detection value and the second power detection value, wherein three coordinate axes of the three-dimensional coordinate system include: a first coordinate axis for representing the first power detection value, a second coordinate axis for representing the second power detection value, and a third coordinate axis for representing the value of (k0-k1); the first calibration curve is used to represent: the relationship between the first power detection value, the second power detection value and the value of (k0-k1); The processor is further configured to determine the output power z of the first antenna based on the relationship using the value of (k0-k1), and to adjust the transmission power of the first transmitting end according to the determined output power z of the first antenna.

5. The radio frequency circuit according to claim 4, characterized in that: The processor is used to determine a first coordinate point in a second calibration curve in a two-dimensional projection coordinate system according to the first power detection value and the second power detection value, wherein the two-dimensional projection coordinate system is a coordinate system composed of the first coordinate axis and the second coordinate axis, the second calibration curve is a curve obtained by projecting the first calibration curve onto the two-dimensional projection coordinate system, the first coordinate point is a position point in the second calibration curve that is closest to the second coordinate point, and the second coordinate point is a coordinate position point corresponding to the first power detection value and the second power detection value in the two-dimensional projection coordinate system; The processor is further configured to determine a third coordinate point corresponding to the first coordinate point in the first calibration curve, and the processor is further configured to determine a coordinate value corresponding to the third coordinate point in the third coordinate axis as the value of (k0-k1).

6. The radio frequency circuit according to claim 1, characterized in that: The radio frequency circuit further comprises a microstrip coupler, and the output end of the combiner is electrically connected to the first antenna via a first transmission line; The radio frequency integrated circuit is electrically connected to the output end of the combiner through the microstrip coupler and the first transmission line in sequence, wherein the microstrip coupler is coupled to the first transmission line.

7. The radio frequency circuit according to claim 6, characterized in that: The radio frequency circuit further includes a second switch component, the radio frequency integrated circuit includes a first coupling end, the first coupling end is electrically connected to the coupling end of the first coupler through the second switch component, and the first coupling end is also electrically connected to the output end of the microstrip coupler through the second switch component; When the second switch is in the first state, the first coupling end is connected to the coupling end of the first coupler, and the first coupling end is disconnected from the output end of the microstrip coupler; When the second switch element is in the second state, the first coupling end is disconnected from the coupling end of the first coupler, and the first coupling end is connected to the output end of the microstrip coupler.

8. The radio frequency circuit according to claim 6, characterized in that: The radio frequency integrated circuit comprises a first coupling end, a second coupling end, a first signal output end and a second signal output end, the first signal output end is a signal output end corresponding to the first coupling end, the second signal output end is a signal output end corresponding to the second coupling end, the first coupling end is electrically connected to the coupling end of the first coupler, and the second coupling end is electrically connected to the output end of the microstrip coupler; The radio frequency circuit further includes a subtractor, the processor includes a first detection end, the first signal output end is electrically connected to the first input end of the subtractor, the second signal output end is electrically connected to the second input end of the subtractor, and the output end of the subtractor is electrically connected to the first detection end; The processor is used to adjust the transmission power of the first transmitting end according to the output result of the subtractor.

9. The radio frequency circuit according to claim 8, characterized in that: The processor further includes a second detection terminal, and the radio frequency circuit further includes a third switch element, a fourth switch element and a fifth switch element; The first signal output terminal is electrically connected to the input terminal of the third switch element, the first output terminal of the third switch element is electrically connected to the first input terminal of the subtractor, the output terminal of the subtractor is electrically connected to the first input terminal of the fourth switch element, the second output terminal of the third switch element is electrically connected to the second input terminal of the fourth switch element, and the output terminal of the fourth switch element is electrically connected to the first detection terminal; The second signal output terminal is electrically connected to the input terminal of the fifth switch element, the first output terminal of the fifth switch element is electrically connected to the second input terminal of the subtractor, and the second output terminal of the fifth switch element is electrically connected to the second detection terminal.

10. An electronic device, characterized in that: The radio frequency circuit comprises the radio frequency circuit as claimed in any one of claims 1 to 9.

Images