Radio frequency power real-time detection device and method

Abstract

The invention discloses a radio frequency power real-time detection device and method. A synthesis end of a power divider is used for inputting a radio frequency signal, and two distribution ends of the power divider are respectively connected with a double-pole M-throw switch; the amplitude processing circuits are connected with the output ends of the double-pole M-throw switches in a one-to-one correspondence manner, the amplitude processing circuits and the detection circuits are connected in series in a one-to-one correspondence manner, and all the output ends of the detection circuits are connected with the real-time detection unit; the real-time detection unit is used for detecting the output of the detection circuit, determining a current detection interval according to a detection result and generating a code, controlling the double-pole M-throw switch to gate the two amplitude processing circuits corresponding to the current detection interval by adopting the code, and controlling the double-pole M-throw switch when the code changes, so that the current detection interval is detected. And continuously sending the at least one radio frequency signal to an amplitude processing circuit and a detection circuit corresponding to the current detection interval for detection. According to the invention, through cooperative work of all components, large-dynamic high-precision radio frequency power detection is realized without missing detection in a full time domain.

Description

Technical Field

[0001] The present invention relates to the field of radio frequency detection technology, and in particular to a device and method for real-time detection of radio frequency power. Background Art

[0002] With the continuous development and advancement of communication and communication countermeasure technologies, transmitter output power in some applications requires continuous, real-time detection capabilities with large dynamic ranges. For example, in order to effectively and effectively evaluate the effectiveness of communication interference in real time, the input signal of the power amplifier used in some drone interference assessment systems is the drone signal received by the assessment system. Because of its small amplitude and large dynamic range, the output power detection of the power amplifier must have large dynamic range and high precision. At the same time, because the input signal amplitude is a rapidly changing signal, in order to promptly track and respond to this signal, the RF output power detection system needs to have full-time domain real-time detection capabilities. Summary of the Invention

[0003] In view of this, an embodiment of the present invention provides a device and method for real-time detection of radio frequency power, aiming to achieve large dynamic and high-precision real-time detection of radio frequency signals in the entire time domain, so as to solve the problems existing in the background technology.

[0004] To achieve the above-mentioned object, according to a first aspect of an embodiment of the present invention, there is provided a real-time detection device for radio frequency power, comprising a power divider, a double-pole M-throw switch, M amplitude processing circuits, M-1 detection circuits, and a real-time detection unit, where M is a natural number greater than or equal to 4;

[0005] The combining end of the power divider is used to input the radio frequency signal, and the two distribution ends are respectively connected to the first input end and the second input end of the double-pole M-throw switch;

[0006] The M input terminals of the M amplitude processing circuits are connected to the M output terminals of the double-pole M-throw switch in a one-to-one correspondence, wherein the output terminal of one amplitude processing circuit is grounded, and the remaining amplitude processing circuits are connected to the M-1 detection circuits in a one-to-one correspondence in series, and all the output terminals of the M-1 detection circuits are connected to the real-time detection unit;

[0007] The real-time detection unit is used to detect the outputs of M-1 detection circuits, determine the current detection interval and generate a code based on the detection results, use the code to control the double-pole M-throw switch to select the two amplitude processing circuits corresponding to the current detection interval, and control the double-pole M-throw switch when the code changes to continuously send at least one RF signal to the amplitude processing circuit and detection circuit corresponding to the current detection interval for detection.

[0008] Furthermore, the radio frequency signal is processed by the coupling adjustment circuit and then input into the synthesis terminal of the power divider;

[0009] The transmission coefficient G of the coupling adjustment circuit is determined according to the following formula:

[0010] G=P d -P0·C+3+IL1+IL2+IL3

[0011] Among them, P d represents the maximum input power of the optimal dynamic range of the detection circuit; P0 represents the maximum output power of the RF signal output by the power amplifier; C represents the coupling degree of the coupler of the power amplifier; IL1 represents the insertion loss of the power divider; IL2 represents the insertion loss of the double-pole M-throw switch; IL3 represents the transmission coefficient in the amplitude processing circuit.

[0012] Furthermore, the power divider is a two-way unidirectional power divider, including an input end and two output ends, and the amplitudes and phases of the two output ends are the same.

[0013] Furthermore, each set of amplitude processing circuits and detection circuits connected in series constitutes a detection channel. The types of amplitude processing circuits include attenuation processing circuits, direct processing circuits, and amplification processing circuits. The corresponding detection channels are attenuation channels, direct processing channels, and amplification channels.

[0014] The optimal dynamic range DR2 of each detection circuit is greater than DR1 / (N1+N2+N3), where DR1 is the power dynamic range of the power amplifier RF output, and N1, N2, and N3 are the number of attenuation channels, through channels, and amplification channels, respectively.

[0015] Furthermore, the attenuation processing circuit performs attenuation processing on the radio frequency signal, and the attenuation coefficients are ranked Nth. i The attenuation coefficient of the attenuation processing circuit is equal to (DR1-DR2)N i / (N1+N3); the through-processing circuit performs through-processing on the radio frequency signal, and the amplification processing circuit amplifies the radio frequency signal, and the Nth order of the amplification coefficient is used. j The amplification factor of the amplification processing circuit is equal to (DR1-DR2)N j / (N1+N3).

[0016] Furthermore, the dynamic ratios of the detection channels are the same, the detection intervals of the detection channels are different but overlap with each other, and the overlap size of adjacent detection intervals is DR2-(DR1-DR2) / (N1+N3).

[0017] Furthermore, the real-time detection unit includes M-1 hysteresis comparators, a power processing and encoding unit, and a gear recognition unit;

[0018] The output ends of the M-1 detection circuits are connected to the power processing and encoding unit and are connected to the input ends of the M-1 hysteresis comparators in a one-to-one correspondence. The output ends of the M-1 hysteresis comparators are connected to the power processing and encoding unit. The power processing and encoding unit is connected to the gear recognition unit.

[0019] The power processing and encoding unit calculates and outputs the power value based on the output of the detection circuit corresponding to the current detection interval;

[0020] The power processing and encoding unit encodes according to the outputs of M-1 hysteresis comparators, and the gear position identification unit selects the double-pole M-throw switch according to the encoding to connect the two amplitude processing circuits.

[0021] Furthermore, the UT- voltage of the hysteresis comparator is located at the lowest end of the detection interval of the connected detection circuit, and the UT+ voltage of the hysteresis comparator is located at the highest end of the next level detection interval of the connected detection circuit.

[0022] Furthermore, the gear recognition unit determines the switching direction according to the coding change. If the switching direction is to switch to the previous detection interval, the double-pole M-throw switch is controlled to keep the current detection interval connected on one path, and the amplitude processing circuit of the previous detection interval is connected on the other path; if the switching direction is to switch to the next detection interval, the double-pole M-throw switch is controlled to keep the current detection interval connected on one path, and the amplitude processing circuit of the next detection interval is connected on the other path.

[0023] According to a second aspect of an embodiment of the present invention, a method for real-time detection of radio frequency power is provided. Based on the above-mentioned apparatus, the method includes:

[0024] The input radio frequency signal is divided into two radio frequency signals, and the two radio frequency signals are respectively input into two input terminals of the double-pole M-throw switch;

[0025] Detect the output of the detection circuit, determine the current detection interval based on the detection result and generate a code;

[0026] A double-pole M-throw switch is used to control coding to select two amplitude processing circuits corresponding to the current detection interval, and two RF signals are sent to the detection circuit connected to the amplitude processing circuit for power detection;

[0027] The power detection result is output and reported. In parallel, when the code changes, the double-pole M-throw switch is controlled to continuously send at least one RF signal to the amplitude processing circuit and detection circuit corresponding to the current detection interval for detection.

[0028] One embodiment of the invention has the following advantages or beneficial effects:

[0029] The present invention realizes high-power and high-dynamic power detection by adopting a multi-channel detection mode through the coordinated work of a power divider, a double-pole M-throw switch, an amplitude processing circuit, a detection circuit and a real-time detection unit. When the detection channel is not switched, two detection signals are selected to work simultaneously, and the real-time detection unit selects the best one. When the power fluctuation is large and the detection channel needs to be switched, the real-time detection unit ensures that one detection channel works in a relatively optimal state and the other detection channel is quickly switched, thereby realizing high-dynamic and high-precision radio frequency power detection without missed detection in the whole time domain.

[0030] In the present invention, the above-mentioned technical solutions can be combined with each other to achieve more preferred combinations. Other features and advantages of the present invention will be described in the following description, and some advantages will become apparent from the description or be learned through practice of the present invention. The objectives and other advantages of the present invention can be realized and obtained through the contents particularly pointed out in the description and drawings. BRIEF DESCRIPTION OF THE DRAWINGS

[0031] The accompanying drawings are only for the purpose of illustrating particular embodiments and are not to be considered limiting of the present invention. Like reference symbols denote like parts throughout the drawings.

[0032] Figure 1 FIG. 4 is a schematic diagram of main modules of a device for real-time detection of radio frequency power according to an embodiment of the present invention.

[0033] Figure 2 FIG. 4 is a schematic diagram of main modules of a device for real-time detection of radio frequency power according to another embodiment of the present invention.

[0034] Figure 3 FIG. 4 is a schematic diagram of main modules of a device for real-time detection of radio frequency power according to another embodiment of the present invention.

[0035] Figure 4 for Figure 3 The detector in the embodiment shown has square-law detection characteristics.

[0036] Figure 5 for Figure 3 Schematic diagram of dynamic range allocation in the amplitude processing circuit in the illustrated embodiment.

[0037] Figure 6 for Figure 3 Input power value distribution in the amplitude processing circuit in the illustrated embodiment.

[0038] Figure 7 1 and 2 are transmission characteristics of the downlink and uplink hysteresis comparators in the embodiment of the present invention.

[0039] Figure 8 for Figure 3The embodiment shown is a schematic diagram of an encoding using a downlink hysteresis comparator.

[0040] Figure 9 for Figure 3 The embodiment shown is a schematic diagram of coding using an upward hysteresis comparator.

[0041] Figure 10 4 is a flow chart of a method for real-time detection of radio frequency power according to an embodiment of the present invention. DETAILED DESCRIPTION

[0042] The preferred embodiments of the present invention will be described in detail below in conjunction with the accompanying drawings, wherein the accompanying drawings constitute a part of this application and are used together with the embodiments of the present invention to illustrate the principles of the present invention, and are not used to limit the scope of the present invention.

[0043] There are three existing RF coupling detection technologies. Peak power detection is susceptible to interference from harmonic signals, resulting in low detection accuracy when harmonics are high. It is also significantly affected by the signal's peak-to-average ratio, resulting in limited detection dynamic range and accuracy. Logarithmic detection uses a relatively complex internal detector circuit, typically in the form of an integrated circuit. This method also suffers from poor output power detection accuracy at high power levels, making precise control impossible. Average power detection has a moderate detection dynamic range, and the detector is typically also in the form of an integrated circuit. Existing RF coupling detection technologies are unable to achieve the high-precision detection requirements for continuously changing RF signals with large dynamic ranges.

[0044] In order to solve the above problems, the embodiments of the present invention provide a device and method for real-time detection of radio frequency power, which are used in special occasions of large dynamic, high-precision and full-time domain real-time detection.

[0045] According to a first aspect of an embodiment of the present invention, a device for real-time detection of radio frequency power is provided. Figure 1 FIG. 1 is a schematic diagram of the main modules of a real-time radio frequency power detection device according to an embodiment of the present invention. Figure 1 As shown, the radio frequency power real-time detection device includes: a power divider, a double-pole M-throw switch, M amplitude processing circuits, M-1 detection circuits and a real-time detection unit, where M is a natural number greater than or equal to 4.

[0046] The synthesis end of the power divider is used to input radio frequency signals, and the two distribution ends are respectively connected to the first input end and the second input end of the double-pole M-throw switch; the M input ends of the M amplitude processing circuits are connected to the M output ends of the double-pole M-throw switch in a one-to-one correspondence, among which the output end of one amplitude processing circuit is grounded, and the remaining amplitude processing circuits and M-1 detection circuits are connected in series in a one-to-one correspondence, and all the output ends of the M-1 detection circuits are connected to a real-time detection unit; the real-time detection unit is used to detect the outputs of the M-1 detection circuits, determine the current detection interval and generate a code based on the detection results, use the code to control the double-pole M-throw switch to select the two amplitude processing circuits corresponding to the current detection interval, and control the double-pole M-throw switch when the code changes, so as to continuously send at least one radio frequency signal to the amplitude processing circuit and the detection circuit corresponding to the current detection interval for detection.

[0047] Specifically, the working process of the real-time RF power detection device in the embodiment of the present invention is as follows: the amplitude of the RF signal output by the power amplifier is uncertain. When the signal amplitude is large, the input RF power belongs to the high power range, and the two distribution ends of the double-pole M-throw switch selection distributor are respectively connected to the grounded amplitude processing circuit and the amplitude processing circuit with the largest attenuation coefficient among the M amplitude processing circuits, so that after being processed by the amplitude processing circuit with the largest attenuation coefficient, the signal entering the subsequent detection circuit is just at the high end of the optimal dynamic range of the detection circuit; when the input signal is of medium size, the input RF power belongs to the medium power range, and the two distribution ends of the double-pole M-throw switch selection distributor are respectively connected to the amplitude processing channel corresponding to the medium position in the amplitude processing circuit, so that the coupled signal entering the subsequent detection circuit is just at the high end of the optimal dynamic range of the corresponding detection circuit; when the input signal is of small size, the input RF power belongs to the low power range, and the two distribution ends of the double-pole M-throw switch selection distributor are respectively connected to the amplitude processing circuit corresponding to the low position in the amplitude processing circuit, so that the coupled signal entering the subsequent detection circuit is just at the high end of the optimal dynamic range of the corresponding detection circuit.

[0048] Specifically, to meet accuracy requirements in this embodiment, the detection circuit must employ a high-precision detection circuit. However, a single detection circuit, such as a square-law detection circuit where the input signal's RMS voltage and the detection output's DC voltage form a linear relationship, can meet high-precision requirements but cannot satisfy the requirement for large dynamics. Therefore, to overcome the conflict between high accuracy and large dynamics, this embodiment prioritizes detection accuracy and, while doing so, improves the dynamic range through other measures. The RF signal's amplitude is processed segmented and separately, including through attenuation, pass-through, and amplification, to expand the input power range of the single detection circuit and achieve an extended detection dynamic range.

[0049] Specifically, in the embodiment of the present invention, a double-pole M-throw switch is used to ensure the switching of different detection channels, prevent missed detection in a certain time period due to switching delay, and select two paths for simultaneous detection by the double-pole M-throw switch before switching, so that one path is guaranteed to work normally during switching. Regardless of before, during or after switching, the two detection signals are compared and analyzed to select the data of the optimal or better detection channel, thereby achieving real-time detection while ensuring that no missed detection occurs during the detection period.

[0050] Specifically, in this embodiment and some embodiments of the present invention, the power divider is a two-way unidirectional power divider, comprising an input and two outputs, the two outputs having the same amplitude and phase. The two-way unidirectional power divider allows two radio frequency channels to operate simultaneously in the detection state during detection, preventing missed detections due to time delays during switching, which can result in incomplete time domain coverage. The input and output characteristic impedance of the two-way unidirectional power divider is 50 ohms, and the standing wave at the distribution port is consistent and as small as possible. Furthermore, the insertion loss within the operating frequency band is required to be consistent, with minimal in-band fluctuations.

[0051] Specifically, in this embodiment and some embodiments of the present invention, each group of amplitude processing circuits and detection circuits connected in series constitutes a detection channel. The types of amplitude processing circuits include attenuation processing circuits, pass-through processing circuits, and amplification processing circuits. The corresponding detection channels are attenuation channels, pass-through channels, and amplification channels. The optimal dynamic range DR2 of each detection circuit is greater than DR1 / (N1+N2+N3), where DR1 is the power dynamic range of the power amplifier's RF output, and N1, N2, and N3 are the number of attenuation channels, pass-through channels, and amplification channels, respectively.

[0052] Specifically, in this embodiment and some embodiments of the present invention, the attenuation processing circuit performs attenuation processing on the radio frequency signal, and the attenuation coefficients of different attenuation channels are different. i The attenuation coefficient of the attenuation processing circuit is equal to (DR1-DR2)N i / (N1+N3), i=1,2,…,N1; the through-processing circuit performs through-processing on the RF signal, and the amplification processing circuit amplifies the RF signal. The amplification coefficients of different amplification channels are different. The Nth amplification circuit is processed in the order of the amplification coefficients. j The amplification factor of the amplification processing circuit is equal to (DR1-DR2)N j / (N1+N3), j=1,2,…,N3.

[0053] Specifically, in this embodiment and some embodiments of the present invention, the dynamic ratios of the detection channels are the same, the detection intervals of the detection channels are different but overlap with each other, and the overlap size of adjacent detection intervals is DR2-(DR1-DR2) / (N1+N3).

[0054] the following Figure 2 Schematic diagram of the main modules of a real-time RF power detection device according to another embodiment of the present invention. Specifically, in some embodiments of the present invention, the real-time detection unit includes M-1 hysteresis comparators, a power processing and encoding unit, and a gear recognition unit;

[0055] The output ends of the M-1 detection circuits are connected to the power processing and encoding unit and are connected to the input ends of the M-1 hysteresis comparators in a one-to-one correspondence. The output ends of the M-1 hysteresis comparators are connected to the power processing and encoding unit. The power processing and encoding unit is connected to the gear recognition unit.

[0056] The power processing and encoding unit calculates and outputs the power value based on the output of the detection circuit corresponding to the current detection interval;

[0057] The power processing and encoding unit encodes according to the outputs of M-1 hysteresis comparators, and the gear position identification unit selects the double-pole M-throw switch according to the encoding to connect the two amplitude processing circuits.

[0058] Furthermore, in this embodiment and some embodiments of the present invention, the UT- voltage of the hysteresis comparator is located at the lowest end of the detection interval of the connected detection circuit, and the UT+ voltage of the hysteresis comparator is located at the highest end of the next level detection interval of the connected detection circuit.

[0059] Specifically, in this embodiment and some embodiments of the present invention, the gear identification unit determines the switching direction based on the coding change. If the switching direction is to switch to the previous detection interval, the double-pole M-throw switch is controlled to keep the current detection interval connected on one path, and the amplitude processing circuit of the previous detection interval is connected on the other path; if the switching direction is to switch to the next detection interval, the double-pole M-throw switch is controlled to keep the current detection interval connected on one path, and the amplitude processing circuit of the next detection interval is connected on the other path.

[0060] In some other embodiments of the present invention, the radio frequency signal is input to the combining end of the power divider after being processed by the coupling adjustment circuit; the transmission coefficient G of the coupling adjustment circuit is determined according to the following formula:

[0061] G=P d -P0·C+3+IL1+IL2+IL3

[0062] Among them, P d represents the maximum input power of the optimal dynamic range of the detection circuit; P0 represents the maximum output power of the RF signal output by the power amplifier; C represents the coupling degree of the coupler of the power amplifier; IL1 represents the insertion loss of the power divider; IL2 represents the insertion loss of the double-pole M-throw switch; IL3 represents the transmission coefficient in the amplitude processing circuit.

[0063] For different systems, the amplitude of the coupling adjustment circuit is set based on the system power, the coupling degree of the coupler, and the optimal dynamic range of the detector. The function of the coupling amplitude adjustment circuit is to perform attenuation adjustment when the coupling degree of the RF signal is too large, so that the coupling signal amplitude is suitable for normal operation in the subsequent circuit. When the coupling degree of the coupler is too small, the amplification adjustment is performed to make the coupling signal amplitude suitable for normal operation in the subsequent circuit. This allows the RF power real-time detection device in the embodiment of the present invention to adapt to the coupling degrees of different power amplifiers, expanding its scope of use. The input end of the coupling amplitude adjustment circuit is connected to the forward coupling end of the coupler of the RF signal power amplifier, and the output end is connected to the synthesis end of the power divider.

[0064] Figure 3 Schematic diagram of the main modules of the radio frequency power real-time detection device according to another embodiment of the present invention, Figure 3 As shown, the radio frequency power real-time detection device in this embodiment of the present invention includes a power divider, a double-pole four-throw switch, four amplitude processing circuits, three detection circuits and a real-time detection unit.

[0065] The power divider is a two-way unidirectional power divider. The combined end of the two-way unidirectional divider is connected to the output end of the coupling amplitude adjustment circuit. The input end of the coupling amplitude adjustment circuit is connected to the forward coupling output end of the coupler. The signals output by the two distribution ends are 3dB less than the forward coupling signal. The two distribution ends 1 and distribution end 2 are respectively connected to the two input ends of the double-pole four-way switch IN 1 and IN 2.

[0066] The structure of the double-pole four-throw switch circuit is as follows Figure 3 As shown, the characteristic impedance of each of the six ports is 50 ohms. The switch control center within the switch receives the switch selection code information from the gear position identification unit within the real-time detection unit to complete the selection control of the double-pole four-throw switch. The present invention can implement a variety of switch combinations. In this embodiment, to simplify control and increase switching speed, the present invention uses the following three combinations for illustration: Combination 1: Input 1 → Output 1, Input 2 → Output 2; Combination 2: Input 1 → Output 3, Input 2 → Output 2; Combination 3: Input 1 → Output 3, Input 2 → Output 4. The above combination arrangement can prevent one circuit from operating in an optimal state while another circuit operates in an overpower detection state, thus avoiding damage to the detection circuit.

[0067] Four amplitude processing circuits form a 4-channel amplitude processing circuit, designed to increase dynamic range while maintaining accuracy. The initial detection state is as follows: In the first channel, one end of the 50-ohm resistor is connected to output port 1 of a double-pole, four-throw switch, and the other end is grounded. In the second channel, the attenuation circuit has both 50-ohm input and output characteristic impedances, one end connected to output port 2 of the double-pole, four-throw switch, and the other end connected to the input of detection circuit 1, corresponding to the high-power detection range. The third channel is a pass-through circuit, with both 50-ohm input and output characteristic impedances. Its input is connected to output port 3 of the double-pole, four-throw switch, and its output is connected to the input of detection circuit 2, corresponding to the medium-power detection range. The fourth channel is an amplifier circuit, with both 50-ohm input and output characteristic impedances. Its input is connected to output port 4 of the double-pole, four-throw switch, and its output is connected to the input of detection circuit 3, corresponding to the low-power detection range. The above 4-channel amplitude processing circuit is sufficient for most applications. Therefore, the first amplitude processing circuit is grounded through a 50-ohm resistor, the second amplitude processing circuit is an attenuation processing circuit with an attenuation coefficient of (DR1-DR2) / 2, the third amplitude processing circuit is a direct pass circuit, and the fourth amplitude processing circuit is an amplification processing circuit with an amplification coefficient of (DR1-DR2) / 2.

[0068] The detection circuit is a square-law detection circuit. Three detection circuits form a three-channel detection circuit. The input of detection circuit 1 is connected to the output of the attenuation processing circuit, and the output of detection circuit 1 is connected to the input of hysteresis comparator A and the power processing and encoding unit in the real-time detection unit. The input of detection circuit 2 is connected to the output of the through-channel, and the output of detection circuit 2 is connected to the input of hysteresis comparator B and the power processing and encoding unit in the real-time detection unit. The input of detection circuit 3 is connected to the output of the amplification processing circuit, and the output of detection circuit 3 is connected to the input of hysteresis comparator C and the power processing and encoding unit in the real-time detection unit. The optimal dynamic detection range DR2 of each detection circuit must be greater than DR1 / 3.

[0069] The real-time detection unit includes a hysteresis comparator A, a hysteresis comparator B, a hysteresis comparator C, a power processing and encoding unit, and a gear identification unit. In an embodiment of the present invention, when there is a slight change in power near the threshold, the use of a general comparator will cause the detection circuit to switch frequently, introduce parasitic interference of the switching frequency, and affect the detection accuracy. The use of a hysteresis comparator can eliminate the disturbance of the interference signal to the detection and the power will not affect the detection accuracy when it jumps frequently at the junction of each gear, maintain a relatively stable detection process, and ensure that the jump across the detection interval is not frequent. The input end of the hysteresis comparator A is connected to the output end of the detection circuit 1, and the output end is connected to the power identification and processing unit; the input end of the hysteresis comparator B is connected to the output end of the detection circuit 2, and the output end is connected to the power identification and processing unit; the input end of the hysteresis comparator C is connected to the output end of the detection circuit 3, and the output end is connected to the power identification and processing unit.

[0070] Specifically, such as Figure 3 As shown, the RF power real-time detection device works together with the power amplifier to complete the full-time domain, real-time automatic detection of the power amplifier output power without omission, and can achieve high-dynamic and high-precision RF signal detection. The power amplifier includes a power amplification unit and a coupler.

[0071] Assume that the output power of the power amplifier is P o , the forward coupling degree is C, then the forward coupling signal amplitude P output from the forward coupling end of the power amplifier coupler is FWD =P o *C, when P o =1000W=60dBm, in the absence of a coupling amplitude adjustment circuit, if the coupling degree of C is large, the signal sent to the 4-channel amplitude processing circuit after passing through the two-way co-directional power divider and the double-pole four-throw switch is too large. If the attenuation of the attenuation channel is increased, the square-law detector may not operate optimally. Similarly, if the coupling degree of C is small, the signal sent to the 4-channel amplitude processing circuit after passing through the two-way co-directional power divider and the double-pole four-throw switch is too small. If the amplification factor of the amplification channel is increased, the square-law detector may not operate optimally. Therefore, in this embodiment, when the coupling degree is large, the coupling amplitude adjustment circuit selects the attenuation circuit, and when the coupling degree is small, the coupling amplitude adjustment circuit selects the amplification circuit. The real-time RF power detection device of the present invention can effectively adapt to the coupling degrees of different power amplifiers, and has flexibility and adaptability.

[0072] The transmission coefficient (gain or attenuation) of the coupling amplitude adjustment circuit is G, which can be positive or negative. Positive values ​​indicate amplification, while negative values ​​indicate attenuation. The two-way co-directional power divider has a distribution loss of -3dB, with insertion loss denoted as IL1. The total divider loss is -3dB-IL1. The insertion loss of the double-pole, four-throw switch is denoted as IL2. The maximum input power for the detector's optimal dynamic range is 8.6dBm. After the forward-coupled signal passes through the coupling amplitude adjustment circuit, the two-way co-directional power divider, the double-pole, four-throw switch, and the amplitude processing circuits for attenuation, pass-through, and amplification, its amplitude must remain within the optimal detection range. The input RF signal power range is 0.1W to 1000W, and the power amplifier's RF output power dynamic range is required to be log(1000W / 0.1W) = 40dB. At full power of 1000W (60dBm), the transmission coefficient G of the coupled amplitude adjustment circuit must satisfy: G = -60*C + 3 + IL1 + IL2 + IL3 + 8.6, where IL3 is the attenuation of the attenuation channel in the multi-channel amplitude processing circuit.

[0073] Furthermore, in this embodiment, 3-channel square-law detection is adopted, which requires that the optimal detection dynamic range of the detector is greater than 40dB / 3=13.33dB. Figure 5 is the square law detection characteristic of the detector in this embodiment. Figure 4 The detector circuit has an optimal operating range of -7dBm to +8.6dBm, which is the linear operating range. The optimal detection dynamic range is 15.6dB. In practice, the 15dB dynamic range of -6.4dBm to +8.6dBm is selected (which meets the requirement of greater than 13.33dB).

[0074] like Figure 3 As shown, one of the 4-channel amplitude processing circuits is grounded through a 50-ohm resistor, and the remaining three channels are connected to the detection circuit, namely the attenuation channel, the pass-through channel, and the amplification channel. In order to facilitate the processing of the detection data by the real-time detection unit, the dynamic ratios of the three channels are distributed as consistently as possible. Figure 5 for Figure 3 The dynamic range distribution diagram in the amplitude processing circuit in the embodiment shown is as follows. Figure 5 As shown. Because (15dB*3-40dB) / (3(number of attenuation channels+number of direct channels+number of amplification channels)-1)=2.5dB, the attenuation channel belonging to the high power gear and the direct channel of the medium power gear have an overlap of 2.5dB, and the direct channel belonging to the medium power gear and the amplification channel of the low power gear also have an overlap of 2.5dB. This overlapping interval provides parameters for the upper and lower threshold voltages of the hysteresis comparator. The hysteresis comparator can not only eliminate detection interference, but also one of the detection circuits often works in a better detection interval when the RF power changes, and the other can seamlessly switch to a better detection channel for the band gear. In combination with the characteristics of the detector of this embodiment and the number of detection channels, the power amplitude of the input end of the 4-channel amplitude processing circuit is distributed, as shown in Figure 6 As shown in the figure, the distribution principle is that the medium power through channel operates in the 15dB dynamic range of -6.4dBm to +8.6dBm. Figure 6 It can be seen that the input signal of the attenuation channel at high power is in the 15dB dynamic range of 6.1dBm to +21.1dBm. In order for the subsequent square law detector 1 to work in the optimal 15dB dynamic range of -6.4dBm to +8.6dBm, the attenuation IL3 required by the attenuation channel is 12.5dB. Figure 6 It can be seen that the input signal of the amplifier channel at low power is in the 15dB dynamic range of -18.9dBm to -3.9dBm, which ensures that the subsequent square-law detector 3 operates in the optimal 15dB dynamic range of -6.4dBm to +8.6dBm. The required amplification factor G1 of the amplifier channel is 12.5dB.

[0075] See also Figure 3 In this embodiment, the initial state is set to high power to effectively prevent damage to the detector caused by operating at overpower. The double-pole, four-throw switch operates in combination 1: input 1 → output 1, input 2 → output 2. The detection channels are respectively a 50 ohm resistor to ground position and a 12.5dB attenuation position. The 12.5dB attenuation position connects to detection circuit channel 1.

[0076] Figure 7 1 and 2 are transmission characteristics of the downlink and uplink hysteresis comparators in the embodiment of the present invention. Figure 8 for Figure 3 The embodiment shown is a schematic diagram of an encoding using a downlink hysteresis comparator.

[0077] The power processing and encoding unit encodes the three detection signals (high, medium, and low power) and the three level signals provided by the three comparators into an ABC code for identification and processing. The gear recognition unit decodes the code provided by the power processing and encoding unit and sends it to the switch control center of the double-pole, four-throw switch for switching, ensuring that the detection circuit operates within the optimal detection range. The UT- and UT+ voltages of the hysteresis comparator are at the lowest end of the current square-law detection optimal detection range and the highest end of the square-law detection detection range for the next power level, respectively.

[0078] like Figure 7 and Figure 8 As shown in the figure, when the power amplifier operates in the high power range and the downstream hysteresis comparator circuit is used, the detection voltage is greater than UT+(1.131V), the output of hysteresis comparator A is low level (0), while the outputs of the other two hysteresis comparators B and C are high level (1) because they have no detection input. According to the output level of the hysteresis comparator, the code ABC=011 can be obtained. When the output power decreases and the detection circuit 1 is between UT-(0.819V) and UT+(1.131V), the output of downstream hysteresis comparator A continues to be low level (0), and the outputs of the other two hysteresis comparators B and C are high level (1), resulting in the code ABC=011.

[0079] When the output power of the high power gear continues to decrease, the detection voltage of the detection circuit 1 is lower than UT-(0.819V), and the output of the downstream hysteresis comparator A is high level (1). At this time, the code ABC switches from 011 to 111. The power processing of the real-time detection unit and the encoding unit perform the switching processing of the detection channel according to the signal change. After decoding by the gear recognition unit, it is sent to the double-pole four-throw switch for switching. Its operation is processed according to combination 2: when ABC changes from 011→111, input 1→output 3 acts, and input 2→output 2 does not act, that is, input 2→output 2 of the detection channel 1 continues to work in a better detection state, and the switching of the detection channel (input 1→output 3) is completed at the same time. At this time, the detection voltage of the detection circuit 2 is greater than UT+(1.131V), the output of the hysteresis comparator A is high level (1), the output of the hysteresis comparator B is low level (0), and the output of the hysteresis comparator C is high level (1) because there is no detection input, then the code ABC=101. When the output power continues to decrease and the detection circuit 2 is between UT-(0.819V) and UT+(1.131V), the downstream hysteresis comparator A continues to output a high level (1), the hysteresis comparator B continues to output a low level (0), and the hysteresis comparator C outputs a high level (1), maintaining code ABC=101.

[0080] When the output power continues to decrease (the power gear is already in the low power gear), the detection voltage is lower than UT-(0.819V), and the output of the downstream hysteresis comparator B is high level (1). At this time, ABC switches from 101 to 111. The power processing and encoding unit of the real-time detection unit switches the detection channel according to the signal change. After decoding by the gear recognition unit, it is sent to the double-pole four-throw switch for switching. The operation process is processed according to combination 3: when ABC changes from 101 to 111, input 1 to output 3 does not work, input 2 to output 4, and at this time, input 1 to output 3 of detection channel 1 continues to work in a better detection state, and the switching of the detection channel (input 2 to output 4) is completed at the same time. The code after switching is ABC=110. At this time, the detection voltage of the detection circuit 3 is greater than UT+(1.131V). The output of the hysteresis comparator A is high level (1) because there is no detection input. The output of the hysteresis comparator B is high level (1), and the output of the hysteresis comparator C is low level (0). The code ABC=110. This combination can realize the detection function of the minimum power (0.1W).

[0081] Similarly, the process of increasing power from low power to high power is as follows. At this time, the double-pole 4-throw switch works in combination 3: input 1 → output 3, input 2 → output 4; Figure 8As shown, if the detection voltage of detection circuit 3 is between UT-(0.819V) and UT+(1.131V), then at this time, there is no voltage in detection circuit 1, so the output of hysteresis comparator A is high level (1), while the detection voltage of detection circuit 2 is less than UT-(0.819V), so the output of hysteresis comparator B is high level (1), and the output voltage of detection circuit 3 is greater than UT-(0.819V), so the output of hysteresis comparator C is low level (0), and code ABC = 110. When the output power increases and detection circuit 2 is between UT-(0.819V) and UT+(1.131V), the output of downstream hysteresis comparator A continues to be high level (1), while the detection voltage of detection circuit 2 is less than UT+(1.131V), so the output of hysteresis comparator B is high level (1), and the output of hysteresis comparator C continues to be low level (0), and code ABC = 110.

[0082] When the output power of the low power gear continues to increase, when the detection voltage of the square law detector 3 is 4.589V, the corresponding detection voltage of the square law detector 2 is UT+(1.131V). After the power continues to increase (the power gear is the medium power gear at this time), the hysteresis comparator B at this time continues to output a high level (1), the downstream hysteresis comparator B outputs a low level (0), and the downstream hysteresis comparator C continues to output a low level (0). Code ABC switches from 110 to 100. At this time, the power processing of the real-time detection unit and the encoding unit switch the detection channel according to the signal change. After encoding through the gear recognition unit, it is sent to the double-pole four-throw switch for switching. The operation process is processed according to combination 2: when code ABC changes from 110 to 100, input 1 to output 3 does not work, input 2 to output 2 works, that is, input 1 to output 3 of detection channel 2 continues to work in a better detection state, and the switching of the detection channel (input 2 to output 2) is completed at the same time. After the switching is completed, code ABC = 101. When the output power continues to increase and the detection circuit 2 is between UT+(1.131V) and 4.589V, the downstream hysteresis comparator A continues to output a high level (1), the hysteresis comparator B continues to output a low level (0), and the hysteresis comparator C outputs a high level (1), maintaining code ABC = 101.

[0083] When the output power of the medium power gear continues to increase, when the detection voltage of the detection circuit 2 is 4.589V, the detection voltage of the corresponding detection circuit 1 is UT+(1.131V). After the power continues to increase (the power gear is the high power gear at this time), the hysteresis comparator A outputs a low level (0) because the detection voltage of the corresponding detection circuit 1 is greater than UT+(1.131V). The downstream hysteresis comparator A outputs a low level (0), the downstream hysteresis comparator B continues to output a low level (0), and the downstream hysteresis comparator C continues to output a high level (1), that is, ABC switches from 101 to 001. At this time, the power processing and encoding unit of the real-time detection unit switches the detection channel according to the signal change. After encoding through the gear recognition unit, it is sent to the double-pole four-throw switch for switching. The operation process is processed according to combination 1: when the code ABC changes from 101 to 001, input 1 to output 1 is in action, and input 2 to output 2 is not in action. That is, input 2 to output 2 of detection channel 2 continues to work in a better detection state, and the switching of the detection channel (input 1 to output 1) is completed at the same time. After the switching is completed, the code ABC = 011. This combination can realize the detection function of the maximum power (1000W).

[0084] Similarly, if Figure 7 and Figure 9 As shown, the uplink hysteresis comparator can also complete the seamless switching of the above detection power levels, just by reversing the high and low levels of the ABC code.

[0085] This embodiment is described with the number of channels M=4. When a larger dynamic range is required, the dynamic range expansion function can be achieved by increasing the number of output terminals (M) of the double-pole M-throw switch, the number of amplitude processing circuit channels (M), the number of detection circuits (M-1), and the number of hysteresis comparator circuits (M-1). Finally, power level coding is added to the power identification and processing center.

[0086] It is understandable that these embodiments of the present invention can set M-1 power levels, which are encoded as M-1 bits and correspond to power levels in order from high to low power. Of the M outputs of the double-pole M-throw switch, one output end is grounded through a 50-ohm resistor as a protection port, and the remaining M-1 output ends are connected to M-1 detection channels (amplitude processing circuit and detection circuit connected in series), thereby preventing one path from operating in the optimal state while the other path operates in the over-power detection state, thereby avoiding damage to the detection circuit. Specifically, the first output end of the double-pole M-throw switch is grounded, and the remaining M-1 output ends are connected to M-1 detection channels in order from high to low power.

[0087] If a downlink hysteresis encoder is used, the power processing and encoding unit performs M-1 bit encoding based on the output of M-1 hysteresis comparators. The M-1 bit encoding is recorded as x1x2…x t …x M-1,t=1,2,…,M-1, if the optimal detection interval of RF power detection is the tth level, x t =0, the rest of the code bits are equal to 1. When a code change is detected and all bits of the M-1 code are 1, the double-pole M-throw switch connects the amplitude adjustment circuit (detection channel) of the t-th gear while keeping the amplitude adjustment circuit (detection channel) of the t-th gear connected. When a code change is detected and all bits of the M-1 code except x are 1, the double-pole M-throw switch connects the amplitude adjustment circuit (detection channel) of the t-th gear while keeping the amplitude adjustment circuit (detection channel) of the t-th gear connected. t =x t-1 =0 and the rest of the bits are 1, the double-pole M-throw switch connects the amplitude adjustment circuit (detection channel) of the t-1th gear while keeping the amplitude adjustment circuit (detection channel) of the t-th gear connected.

[0088] If an uplink hysteresis encoder is used, the power processing and encoding unit performs M-1 bit encoding based on the output of M-1 hysteresis comparators. The M-1 bit encoding is recorded as x1x2…x t …x M-1 ,t=1,2,…,M-1, if the optimal detection interval of RF power detection is the tth level, x t =1, the rest of the code bits are equal to 0. When a code change is detected and all bits of the M-1 code are 0, the double-pole M-throw switch connects the amplitude adjustment circuit (detection channel) of the t-th gear while keeping the amplitude adjustment circuit (detection channel) of the t-th gear connected. When a code change is detected and all bits of the M-1 code except x are 0, the double-pole M-throw switch connects the amplitude adjustment circuit (detection channel) of the t-th gear while keeping the amplitude adjustment circuit (detection channel) of the t-th gear connected. t =x t-1 =1 and the rest of the bits are 0, the double-pole M-throw switch connects the amplitude adjustment circuit (detection channel) of the t-1th gear while keeping the amplitude adjustment circuit (detection channel) of the t-th gear connected.

[0089] According to another aspect of an embodiment of the present invention, a method for real-time detection of radio frequency power is provided, which is based on the real-time detection device for radio frequency power in the above-mentioned embodiment of the present invention. Figure 10 FIG. 1 is a flow chart of a method for real-time detection of radio frequency power according to an embodiment of the present invention. Figure 10 As shown, the method includes:

[0090] Step S101, dividing the input radio frequency signal into two radio frequency signals, and inputting the two radio frequency signals into two input terminals of a double-pole M-throw switch respectively;

[0091] Step S102, detecting the output of the detection circuit, determining the current detection interval based on the detection result and generating a code;

[0092] Step S103, using a code-controlled double-pole M-throw switch to select two amplitude processing circuits corresponding to the current detection interval, and sending two RF signals to the detection circuit connected to the amplitude processing circuit for power detection;

[0093] In step S104, the power detection result is output and reported. In parallel, when the code changes, the double-pole M-throw switch is controlled to continuously send at least one RF signal to the amplitude processing circuit and the detection circuit corresponding to the current detection interval for detection.

[0094] The embodiment of the present invention adopts a two-way unidirectional power distributor in conjunction with a double-pole M-throw switch to achieve simultaneous detection of two detection signals in different detection channels. When one of the detection signals is switched, the double-pole M-throw switch keeps the other signal working, ensuring that one detection signal operates in a relatively optimal range at any time. This ensures that no detection data is lost when switching between detection signals of different power levels, and realizes real-time RF power detection in the entire time domain.

[0095] In the embodiment of the present invention, an amplitude processing circuit is used to attenuate, pass through, and amplify the radio frequency signal. Different output power levels correspond to different optimal detection channels. The attenuation or amplification factor of each amplitude processing circuit is evenly spaced, so that the detection circuit is within the optimal dynamic range at the power level, achieving an expansion of the dynamic range.

[0096] In this embodiment of the present invention, the real-time detection unit encodes the results of the hysteresis comparator and uses this encoding to switch and gate the double-pole M-throw switch, selecting the optimal detection channel. The hysteresis comparator reduces detection disturbances and facilitates the power processing and encoding unit to encode power information. The gear recognition unit simultaneously selects the optimal detection channel. The power processing and encoding unit also calculates the corresponding relationship between power and detection voltage based on the attenuation (gain) values ​​of different detection channels and the characteristics of the detection circuit, converting the detected detection voltage into an accurate power value.

[0097] In the embodiment of the present invention, by setting the detection intervals of different channels to be evenly spaced, it is ensured that coupled signals of different power levels can be switched to the optimal detection channel, the detection circuit works in the optimal state, and the optimal detection of output power is achieved.

[0098] The embodiment of the present invention enables the power amplifier to quickly complete high-precision real-time detection when the amplitude of the input signal is unknown.

[0099] Those skilled in the art will appreciate that all or part of the process steps of the above-described embodiments can be implemented by instructing related hardware through a computer program, and the program can be stored in a computer-readable storage medium, such as a magnetic disk, an optical disk, a read-only memory, or a random access memory.

[0100] The above description is only a preferred specific embodiment of the present invention, but the scope of protection of the present invention is not limited thereto. Any changes or substitutions that can be easily thought of by any technician familiar with this technical field within the technical scope disclosed by the present invention should be covered by the scope of protection of the present invention.

Claims

1. A real-time radio frequency power detection device, characterized in that: It includes a power divider, a double-pole M-throw switch, M amplitude processing circuits, M-1 detection circuits and a real-time detection unit, where M is a natural number greater than or equal to 4; The combining end of the power divider is used to input the radio frequency signal, and the two distribution ends are respectively connected to the first input end and the second input end of the double-pole M-throw switch; The M input terminals of the M amplitude processing circuits are connected to the M output terminals of the double-pole M-throw switch in a one-to-one correspondence, wherein the output terminal of one amplitude processing circuit is grounded, and the remaining amplitude processing circuits are connected to the M-1 detection circuits in a one-to-one correspondence in series, and all the output terminals of the M-1 detection circuits are connected to the real-time detection unit; The real-time detection unit is used to detect the outputs of M-1 detection circuits, determine the current detection interval and generate a code based on the detection results, use the code to control the double-pole M-throw switch to select the two amplitude processing circuits corresponding to the current detection interval, and control the double-pole M-throw switch when the code changes to continuously send at least one RF signal to the amplitude processing circuit and detection circuit corresponding to the current detection interval for detection.

2. The device according to claim 1, characterized in that The radio frequency signal is processed by the coupling adjustment circuit and input into the synthesis end of the power divider; The transmission coefficient G of the coupling adjustment circuit is determined according to the following formula: G=P d -P0·C+3+IL1+IL2+IL3 Among them, P d represents the maximum input power of the optimal dynamic range of the detection circuit; P0 represents the maximum output power of the RF signal output by the power amplifier; C represents the coupling degree of the coupler of the power amplifier; IL1 represents the insertion loss of the power divider; IL2 represents the insertion loss of the double-pole M-throw switch; IL3 represents the transmission coefficient in the amplitude processing circuit.

3. The device according to claim 1, characterized in that The power divider is a two-way unidirectional power divider, comprising an input end and two output ends, wherein the amplitudes and phases of the two output ends are the same.

4. The device according to claim 1, characterized in that Each set of amplitude processing circuits and detection circuits connected in series constitutes a detection channel. The types of amplitude processing circuits include attenuation processing circuits, direct processing circuits, and amplification processing circuits. The corresponding detection channels are attenuation channels, direct processing circuits, and amplification channels. The optimal dynamic range DR2 of each detection circuit is greater than DR1 / (N1+N2+N3), where DR1 is the power dynamic range of the power amplifier RF output, and N1, N2, and N3 are the number of attenuation channels, through channels, and amplification channels, respectively.

5. The device according to claim 4, characterized in that The attenuation processing circuit attenuates the RF signal and the Nth order is in the order of attenuation coefficient. i The attenuation coefficient of the attenuation processing circuit is equal to (DR1-DR2)N i / (N1+N3); the through-processing circuit performs through-processing on the radio frequency signal, and the amplification processing circuit amplifies the radio frequency signal, and the Nth order of the amplification coefficient is used. j The amplification factor of the amplification processing circuit is equal to (DR1-DR2)N j / (N1+N3).

6. The device according to claim 4, characterized in that The dynamic ratios of the detection channels are the same, the detection intervals of the detection channels are different but overlap with each other, and the overlap size of adjacent detection intervals is DR2-(DR1-DR2) / (N1+N3).

7. The device according to claim 6, characterized in that The real-time detection unit includes M-1 hysteresis comparators, a power processing and encoding unit, and a gear recognition unit; The output ends of the M-1 detection circuits are connected to the power processing and encoding unit and are connected to the input ends of the M-1 hysteresis comparators in a one-to-one correspondence. The output ends of the M-1 hysteresis comparators are connected to the power processing and encoding unit. The power processing and encoding unit is connected to the gear recognition unit. The power processing and encoding unit calculates and outputs the power value according to the output of the detection circuit corresponding to the current detection interval; The power processing and encoding unit encodes according to the outputs of M-1 hysteresis comparators, and the gear position identification unit selects the double-pole M-throw switch according to the encoding to connect the two amplitude processing circuits.

8. The device according to claim 7, characterized in that The UT- voltage of the hysteresis comparator is located at the lowest end of the detection interval of the connected detection circuit, and the UT+ voltage of the hysteresis comparator is located at the highest end of the next level detection interval of the connected detection circuit.

9. The device according to claim 7, characterized in that The gear recognition unit determines the switching direction according to the code change. If the switching direction is to switch to the previous detection interval, the double-pole M-throw switch is controlled to keep the connection of the current detection interval on one path, and the other path is connected to the amplitude processing circuit of the previous detection interval; if the switching direction is to switch to the next detection interval, the double-pole M-throw switch is controlled to keep the connection of the current detection interval on one path, and the other path is connected to the amplitude processing circuit of the next detection interval.

10. A method for real-time detection of radio frequency power, characterized in that: Based on the device according to any one of claims 1 to 9, the method comprises: The input radio frequency signal is divided into two radio frequency signals, and the two radio frequency signals are respectively input into two input terminals of the double-pole M-throw switch; Detect the output of the detection circuit, determine the current detection interval based on the detection result and generate a code; A double-pole M-throw switch is used to control coding to select two amplitude processing circuits corresponding to the current detection interval, and two RF signals are sent to the detection circuit connected to the amplitude processing circuit for power detection; The power detection result is output and reported. In parallel, when the code changes, the double-pole M-throw switch is controlled to continuously send at least one RF signal to the amplitude processing circuit and detection circuit corresponding to the current detection interval for detection.

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