Phase adaptive dynamic calibration compensation method and system based on temperature drift compensation

Abstract

The invention relates to a phase adaptive dynamic calibration compensation method and system based on temperature drift compensation, belongs to the technical field of vibration testing, and solves the problems of poor wide temperature precision of micro-vibration phase calibration, weak multi-frequency adaptation, incomplete full-link compensation, calibration acquisition conflict and fast aging failure in the prior art. The method comprises the following steps: determining an original calibration signal based on an analysis frequency, calculating an initial phase difference according to the original calibration signal, determining a first time compensation amount according to the initial phase difference, and carrying out first calibration compensation; acquiring environment temperature, and establishing a phase compensation model based on the environment temperature, the analysis frequency and the initial phase difference; obtaining the node temperature of the signal transmission link, determining a second time compensation amount by using the phase compensation model, and carrying out second calibration compensation; the information transmission link comprises a plurality of signal transmission nodes. According to the invention, wide temperature range, stable full-link calibration, parallel calibration and acquisition, and adaptive dynamic calibration compensation are realized, so that the micro-vibration measurement accuracy is improved.

Description

Technical Field

[0001] This invention relates to the field of vibration testing technology, and in particular to a phase adaptive dynamic calibration compensation method and system based on temperature drift compensation. Background Technology

[0002] In fields such as precision equipment operation and maintenance (e.g., lithography machines, aero engines), civil engineering structural health monitoring, and geological micro-vibration exploration, the phase difference accuracy of signals between channels of the data acquisition system is a crucial guarantee for achieving vibration source localization, modal parameter identification, and fault early warning during micro-vibration environment site testing.

[0003] Current data acquisition instruments mostly perform phase calibration at room temperature or adjust only through a combination of synchronization windows without temperature adaptation or consideration of end-to-end temperature drift compensation. Furthermore, the calibration signal frequency and calibration model parameters are fixed, making them unsuitable for multiple analysis frequencies and device aging. In addition, the method of interrupting the actual acquisition and switching to the calibration signal during the acquisition process leads to data breakpoints and fails to consider anti-coupling mechanisms, resulting in limited compensation accuracy. Problems include poor wide-temperature calibration compensation accuracy, incomplete end-to-end compensation, calibration acquisition conflicts, and rapid failure of the calibration model due to device aging.

[0004] Therefore, there is an urgent need for an adaptive dynamic calibration compensation method that can adapt to a wide temperature range and achieve stable calibration and parallel calibration and data acquisition across the entire process. Summary of the Invention

[0005] Based on the above analysis, the embodiments of the present invention aim to provide a phase adaptive dynamic calibration compensation method and system based on temperature drift compensation, in order to solve one of the problems in the prior art, such as poor wide-temperature calibration compensation accuracy, incomplete end-to-end compensation, calibration acquisition conflicts, and rapid failure of calibration models due to device aging.

[0006] On one hand, embodiments of the present invention provide a phase adaptive dynamic calibration compensation method based on temperature drift compensation, including: determining the original calibration signal based on the analysis frequency, and calculating the initial phase difference according to the original calibration signal;

[0007] Based on the initial phase difference, determine the first time compensation amount and perform the first calibration compensation; Obtain the ambient temperature, and establish a phase compensation model based on the ambient temperature, the analysis frequency, and the initial phase difference; The node temperature of the signal transmission link is obtained, and the second time compensation amount is determined using the phase compensation model to perform a second calibration compensation; wherein, the information transmission link includes multiple signal transmission nodes.

[0008] Furthermore, based on the analysis frequency, the original calibration signal is determined, including: Obtain the analysis frequency command and identify the analysis frequency of the micro-vibration acquisition device; Based on the analysis frequency, the original calibration signal is generated by a DDS signal generator; wherein the frequency of the original calibration signal is the same as the upper limit of the analysis frequency.

[0009] Further, based on the original calibration signal, the initial phase difference is calculated, including: Based on the original calibration signal, obtain the channel calibration signals for multiple channels; Perform a Fourier transform on the channel calibration signal to obtain the phase value of each channel; Calculate the corresponding initial phase difference based on the phase value of each channel.

[0010] Further, the node temperature of the signal transmission link is obtained, and a second compensation value is determined using the phase compensation model. A second calibration compensation is then performed, including: Obtain the node temperature of each of the signal transmission nodes; Based on the node temperature and the analysis frequency, the phase drift corresponding to different signal transmission nodes is calculated using the phase compensation model. Determine the total phase error based on all the stated phase drift amounts; Based on the total phase error, a second time compensation amount is determined, and a second calibration compensation is performed.

[0011] Furthermore, the phase adaptive dynamic calibration compensation method based on temperature drift compensation also includes: Based on the original calibration signal, the measured calibration signal of the channel is obtained, and the measured phase difference is calculated based on the measured calibration signal of the channel. Based on the measured phase difference, determine the third time compensation amount and perform a third calibration compensation. Further, based on the original calibration signal, the measured calibration signal of the channel is obtained, including: Identify the state of the acquisition frame and determine whether the current frame state is within the acquisition frame gap; If it is within the acquisition frame gap, and the gap duration of the acquisition frame gap is not less than the calibration signal acquisition duration, then the measured calibration signal of the acquisition channel is acquired based on the original calibration signal.

[0012] Furthermore, it also includes: If the data is within the acquisition frame gap, and the gap duration is less than the calibration signal acquisition duration, then a buffer alternation mechanism is used to acquire the measured calibration signal of the channel.

[0013] Further, based on the measured calibration signal of the channel, the measured phase difference is calculated, including: The energy fluctuation of the measured calibration signal of the channel is obtained, and it is determined whether the energy fluctuation exceeds the energy fluctuation threshold. If the energy fluctuation threshold is not exceeded, then the measured calibration signal of the channel is subjected to Fourier transform to obtain the phase value of each channel; If the energy fluctuation threshold is exceeded, the measured calibration signal of the channel is separated, and the separated measured calibration signal of the channel is subjected to Fourier transform to obtain the measured phase value. The measured phase difference is calculated based on the measured phase value.

[0014] Furthermore, it also includes: A phase compensation database is constructed based on the measured phase difference, the analysis frequency, the node temperature, and the total phase error. The model parameters of the phase compensation model are updated based on the phase compensation database.

[0015] On the other hand, embodiments of the present invention provide a phase adaptive dynamic calibration compensation system based on temperature drift compensation, comprising: The first compensation module is used to determine the original calibration signal based on the analysis frequency, calculate the initial phase difference based on the original calibration signal, and determine the first time compensation amount based on the initial phase difference. The model management module is used to acquire the ambient temperature and establish a phase compensation model based on the ambient temperature, the analysis frequency, and the initial phase difference. The second compensation module is used to obtain the node temperature of the signal transmission link and determine the second time compensation amount using the phase compensation model; wherein, the information transmission link includes multiple signal transmission nodes.

[0016] Compared with the prior art, the present invention can achieve at least one of the following beneficial effects: 1. By detecting the temperature of all nodes in the entire link and performing two calibration compensations, the influence of different node temperatures on the phase difference is considered, and the response compensation amount is calculated to achieve calibration stability across a wide temperature range and the entire link. At the same time, a phase compensation model is established to facilitate dynamic adjustment of the calibration compensation amount based on changes in analysis frequency and temperature, thereby improving the phase compensation accuracy after device aging and achieving high-precision, long-term stable phase compensation.

[0017] 2. Generate a corresponding calibration signal based on the analysis frequency, and combine it with the phase compensation model to achieve multi-frequency adaptation, effectively solving the error rebound problem in high-frequency scenarios in existing technologies.

[0018] 3. By acquiring the frame status, channel calibration signals are acquired during the frame intervals to avoid interference with the real signal, improve the continuity of the real data, and further perform a third calibration compensation to achieve full coverage of error sources and improve compensation accuracy. Furthermore, by comparing the interval duration of the acquisition frame interval with the calibration signal acquisition duration, in cases where the interval duration of the acquisition frame interval is less than the calibration signal acquisition duration (i.e., the real data is sampled at high frequency and the sampling frame interval is insufficient to complete the acquisition of a standard signal), a buffer alternation mechanism is adopted to acquire the channel calibration signal, enabling parallel execution of calibration and acquisition and solving the problem of real data breakpoints.

[0019] 4. The energy fluctuation of the calibration signal is measured through the detection channel. For fluctuations exceeding the energy fluctuation threshold, the signal is separated and then Fourier transform is performed to reduce the coupling of real vibration to the calibration loop through the mechanical structure in industrial scenarios, thereby improving calibration accuracy.

[0020] In this invention, the above-described technical solutions can be combined with each other to achieve more preferred combinations. Other features and advantages of this invention will be set forth in the following description, and some advantages may become apparent from the description or be learned by practicing the invention. The objects and other advantages of this invention can be realized and obtained from what is particularly pointed out in the description and drawings. Attached Figure Description

[0021] The accompanying drawings are for illustrative purposes only and are not intended to limit the invention. Throughout the drawings, the same reference numerals denote the same parts. Figure 1 This is a schematic flowchart of a phase adaptive dynamic calibration compensation method based on temperature drift compensation in an embodiment of the present invention. Figure 2 This is a schematic diagram of the main modules of another phase adaptive dynamic calibration compensation system based on temperature drift compensation in an embodiment of the present invention. Detailed Implementation

[0022] Preferred embodiments of the present invention will now be described in detail with reference to the accompanying drawings, which form part of this application and are used together with the embodiments of the present invention to illustrate the principles of the present invention, but are not intended to limit the scope of the present invention.

[0023] A specific embodiment of the present invention discloses a phase adaptive dynamic calibration compensation method based on temperature drift compensation, such as... Figure 1 As shown, it includes: Step S1: Determine the original calibration signal based on the analysis frequency, and calculate the initial phase difference based on the original calibration signal.

[0024] Based on the analysis frequency, the original calibration signal is determined, and then the initial phase difference is calculated based on the original calibration signal. In this embodiment, step S1 is performed when the device is started (cold start / restart). Step S1 specifically includes steps S11-S15.

[0025] Step S11: Obtain the analysis frequency command and identify the analysis frequency of the micro-vibration acquisition device.

[0026] In this embodiment, an ARM (Advanced RISC Machine) is used to obtain the analysis frequency command, identify the analysis frequency of the micro-vibration acquisition device (e.g., the vibration signal frequency that needs to be monitored, 1024Hz), and send control parameters including the analysis frequency to the FPGA (Field Programmable Gate Array) via the SPI bus (Serial Peripheral Interface). For example, the micro-vibration acquisition device refers to a multi-channel data acquisition instrument or system used for micro-vibration environment field testing.

[0027] Step S12: Based on the analysis frequency, generate the original calibration signal using a DDS signal generator; wherein the frequency of the original calibration signal is the same as the upper limit of the analysis frequency.

[0028] In this embodiment, after the FPGA acquires the analysis frequency, it generates an original calibration signal using its built-in DDS (Direct Digital Synthesis) signal generator. Based on the analysis frequency, it generates an appropriate original calibration signal to adapt to different analysis frequencies. For example, the original calibration signal is a standard sine wave with a distortion of less than or equal to 0.01%.

[0029] Furthermore, given that high-frequency signals have the greatest phase delay and the most significant impact on calibration accuracy, the frequency of the original calibration signal is the same as the upper limit of the analysis frequency. That is, the original calibration signal with the same frequency is generated for the upper limit of the analysis frequency of the current working state (e.g., when working at 512Hz, the calibration signal is 512Hz), to ensure accuracy in high-frequency scenarios.

[0030] Step S13: Obtain channel calibration signals for multiple channels based on the original calibration signal.

[0031] Specifically, the original calibration signal is synchronously distributed to multiple channels to obtain the corresponding channel calibration signal. In this embodiment, a power divider is used to synchronously distribute the original calibration signal to the analog switch inputs of multiple channels. The ARM controls the analog switches to switch to the original calibration signal. The AD chip of each channel synchronously acquires the channel calibration signal for a preset number of cycles, which serves as the basis for subsequent phase value calculations. For example, the number of channels is 4, and the preset number of cycles is 10. Further, the channel calibration signal is transmitted to the FPGA via the LVDS (Low Voltage Differential Signaling) bus, and then transmitted to the DSP chip (Digital Processing Chip) via DMA (Direct Memory Access).

[0032] Step S14: Perform a Fourier transform on the channel calibration signal to obtain the phase value of each channel.

[0033] This embodiment employs a 1024-point FFT (Fast Fourier Transform) to perform a Fourier transform on the channel calibration signal for a preset number of periods for each channel, obtaining the phase value of each channel. For example, a DSP chip is used to perform the Fourier transform. The 1024-point FFT used in this embodiment can accurately match different analysis frequencies, avoiding phase value deviations caused by analysis frequency confusion; for the original calibration signal, especially a standard sine wave with a distortion ≤0.01%, the fundamental phase value can be accurately extracted with small calculation errors; and the same Fourier transform method is used for each channel to avoid systematic errors.

[0034] For example, a 1024-point FFT is performed on each of the 10 cycles of the channel calibration signal for each channel to obtain 10 basic phase values ​​for each channel. The average of these 10 basic phase values ​​is then used as the phase value for that channel. In other embodiments, the sum of the 10 basic phase values ​​can also be used as the phase value for that channel. By superimposing multi-cycle data from multiple cycles of channel calibration signals, power supply noise and electromagnetic interference can be canceled, single-cycle random noise interference can be avoided, and the accuracy of phase value extraction can be improved.

[0035] Furthermore, after performing Fourier transform on the channel calibration signals for a preset number of periods for each channel, outliers in the amplitude and phase obtained from the Fourier transform can be removed. Based on the base phase value after removing outlier periods, the channel phase value is calculated to ensure the stability of the subsequent initial phase difference. For example, an outlier period refers to a period in which the amplitude of the channel calibration signal after Fourier transform is an outlier amplitude, or the base phase value is an outlier base phase value. For instance, an amplitude greater than a preset amplitude threshold or N times the average amplitude of multiple periods is defined as an outlier amplitude, and a base phase value greater than a preset phase threshold or M times the average base phase value of multiple periods is defined as an outlier base phase value. The preset amplitude threshold, preset phase threshold, N, and M can be set as needed and are not limited here.

[0036] Step S15: Calculate the corresponding initial phase difference based on the phase value of each channel.

[0037] Based on the phase value of each channel, select one channel as a reference and calculate the initial phase difference for each channel.

[0038] For example, the phase values ​​of the four channels are as follows: , , , Taking channel 1 as the reference, the initial phase differences of the four channels are as follows: , , , .

[0039] Step S2: Determine the first time compensation amount based on the initial phase difference and perform the first calibration compensation.

[0040] Specifically, based on the initial phase difference, the first time compensation amount is calculated using the following formula, and two-stage programmable delay lines are configured using the bus to perform the first calibration compensation for each channel.

[0041] In the formula, This represents the first-time compensation amount for the i-th channel. Let be the initial phase difference of the i-th channel. To analyze frequencies. For example, analyze frequencies. The frequency is 1024Hz, and the initial phase difference of channel 2 is... Then, for channel 2, according to Adjust the time to complete the first calibration compensation.

[0042] In this embodiment, the DSP chip calculates the required first time compensation amount based on the initial phase difference. Two programmable delay lines are configured via the SPI bus, and the delay lines are controlled to adjust their corresponding times according to the first time compensation amount for the first calibration compensation. Here, the delay line refers to a controllable timing adjustment module that introduces a settable time delay into the target signal, causing the timestamp of the output signal to be offset relative to the input signal.

[0043] Calculate the first time compensation amount for each channel, adjust the corresponding time of the control delay line (i.e., set the time delay according to the first time compensation amount), and re-acquire the channel calibration signal to recalculate the initial phase difference until the initial phase difference of all four channels is less than the first phase difference threshold. For example, the first phase difference threshold is... Furthermore, at different analysis frequencies, steps S1-S2 complete the first calibration compensation at each analysis frequency. It is understood that for each analysis frequency, the cumulative first-time compensation amount from multiple adjustments can be recorded, and compensation can be performed according to the records when using the corresponding analysis frequency.

[0044] Step S3: Obtain the ambient temperature, and establish a phase compensation model based on the ambient temperature, the analysis frequency, and the initial phase difference.

[0045] Obtain the ambient temperature, and establish a phase compensation model based on the ambient temperature, analysis frequency, and initial phase difference.

[0046] For example, the phase compensation model is constructed using a linear function. In the formula, Indicates the ambient temperature is Analysis frequency is At that time, the estimated phase difference calculated by the phase compensation model, Indicates analysis frequency The corresponding temperature coefficient can be set based on experience. For example, the temperature coefficient corresponding to an analysis frequency of 128Hz. , For initial calibration at room temperature, Indicates analysis frequency The corresponding initial phase offset can be calculated by combining the analysis frequency obtained in step 1 with the corresponding initial phase difference.

[0047] Furthermore, to improve the accuracy of the phase compensation model, within a wide temperature range, for each channel, at preset temperature intervals, at different ambient temperatures, following steps S11-S15, the initial phase difference corresponding to different analysis frequencies is collected, and the ambient temperature, analysis frequency, and corresponding initial phase difference are recorded as sample data for parameter optimization of the phase compensation model. For example, within the range of -40℃ to 85℃, for each channel, at 10℃ intervals, channel calibration signals for 10 cycles at four analysis frequencies (128Hz / 256Hz / 512Hz / 1024Hz) are collected for 4 channels, and the corresponding initial phase difference is calculated. The sample data is preprocessed to remove outliers, as can be done in step S14. For example, outliers with a basic phase value abruptly exceeding 1° are removed.

[0048] For the preprocessed sample data, the ambient temperature, analysis frequency, and initial phase difference are substituted into the phase compensation model to update the model parameters. For example, when the phase compensation model is constructed using a linear function, the least squares method is used for fitting, and the temperature coefficient is updated. and initial phase offset In this embodiment, the model parameters of the phase compensation model are stored in flash memory integrated inside the DSP chip or externally. It should be noted that a set of model parameters can be determined by fitting sample data from different channels, or a set of model parameters can be fitted separately for each channel based on the corresponding sample data.

[0049] Furthermore, to eliminate the impact of hardware installation and inherent deviations during the process on the phase compensation model, and to make the phase compensation model more focused on the dynamic deviations caused by ambient temperature and analysis frequency, within a wide temperature range, for each channel, according to a preset temperature interval, at different ambient temperatures, following steps S1-S2, the initial phase difference of each channel after the first calibration compensation is collected at different analysis frequencies. The ambient temperature, each analysis frequency, and the corresponding initial phase difference after the first calibration compensation are recorded as sample data for parameter optimization of the phase compensation model.

[0050] Step S4: Obtain the node temperature of the signal transmission link, determine the second time compensation amount using the phase compensation model, and perform a second calibration compensation; wherein, the information transmission link includes multiple signal transmission nodes.

[0051] Specifically, for each channel, the node temperature of the signal transmission link of that channel is obtained, the second time compensation amount is determined using the initial phase compensation model, and the second calibration compensation is performed to achieve dynamic temperature drift compensation across the entire link, specifically including steps S41-S44.

[0052] Step S41: Obtain the node temperature of each of the signal transmission nodes.

[0053] The node temperature of each signal transmission node is acquired. In this embodiment, the signal transmission link includes four signal transmission nodes: a filter node, a SHA (Secure Hash Algorithm) node, an AD node, and an FPGA node. Temperature sensors are used to collect the node temperature of each signal transmission node at temperature sampling intervals. For example, an ADT7410 temperature sensor is mounted on the surface of the corresponding device at each of the four nodes, and the node temperature of the four nodes is collected every 50ms. The temperatures collected by the temperature sensors are uploaded to the ARM via the SPI bus in a time-division multiplexing manner, and then forwarded to the DSP.

[0054] Furthermore, the ambient temperature of each channel in step S3 can be determined by the node temperature. In this embodiment, the ambient temperature is calculated by weighted summation of the temperatures of each node in the channel. The weights can be set to be the same, or they can be set based on historical data or industry experience, according to the contribution ratio of each node's phase drift to the total phase error. For example, the ambient temperature of the i-th channel... , , , , The temperature is measured at four nodes.

[0055] Step S42: Based on the node temperature and the analysis frequency, use the phase compensation model to calculate the phase drift corresponding to different signal transmission nodes.

[0056] The analysis frequency and node temperature are input into the phase compensation model to calculate the estimated phase difference, i.e., the phase drift amount corresponding to each signal transmission node. In this embodiment, the DSP is used to call the phase compensation model to calculate the phase drift amount corresponding to different signal transmission nodes based on the node temperature and analysis frequency.

[0057] For example, the analysis frequency is The node temperature corresponding to the filter node is The phase shift amount corresponding to the filter node .

[0058] Step S43: Determine the total phase error based on all the stated phase drift amounts.

[0059] Specifically, the total phase error of each channel is calculated by superimposing the phase drift of each signal transmission node corresponding to each channel.

[0060] For example, In the formula, This represents the total phase error of the i-th channel (analysis frequency is ). ), This represents the phase shift of the filter node corresponding to the i-th channel (node ​​temperature is...). Analysis frequency is ), This represents the phase shift amount corresponding to the SHA node of the i-th channel (node ​​temperature is...). Analysis frequency is ), This represents the phase shift of the AD node corresponding to the i-th channel (node ​​temperature is...). Analysis frequency is ), This represents the phase shift amount corresponding to the FPGA node of the i-th channel (node ​​temperature is...). Analysis frequency is ).

[0061] Step S44: Determine the second time compensation amount based on the total phase error, and perform a second calibration compensation.

[0062] First, based on the total phase error of each channel, the corresponding second time compensation amount is determined according to the following formula.

[0063] In the formula, This is the second time compensation amount for the i-th channel. This represents the total phase error of the i-th channel (analysis frequency is ). ).

[0064] Then, based on the second time compensation amount corresponding to each channel, a second calibration compensation is performed on each channel. Apart from frequency analysis, only the temperature of each node needs to be acquired to determine the second time compensation amount and perform the second calibration compensation. This does not affect the acquisition of real data (such as the acquisition of vibration response signals by sensors), avoids data gaps, ensures timely response, and resolves phase errors caused by temperature drift.

[0065] Furthermore, based on the distribution of phase drift at each node in the total phase error, calibration compensation nodes are determined, and a second calibration compensation is performed, rather than a forced uniform distribution, to ensure targeted compensation. For example, a mapping relationship is established between the phase drift and the two-stage programmable delay lines. From the phase drift corresponding to each node, the phase drift with the largest value is selected. Based on the mapping relationship, the calibration compensation point is determined. According to the connection relationship between the standard compensation point and the two-stage programmable delay lines, the second calibration compensation is performed by controlling the two-stage programmable delay lines. For instance, if the phase drift of the filter node is the largest, the first-stage delay line (filter output) is adjusted; if the phase drift of the AD node is the largest, the second-stage delay line (AD output) is adjusted; if the phase drift of the SHA node is the largest, the second time compensation is proportionally distributed to the two-stage delay lines for coordinated compensation.

[0066] Furthermore, if the maximum difference between the phase drift amounts of each node is less than the distribution deviation threshold, a second time compensation amount is allocated according to a preset priority and preset compensation weight to ensure that the total phase error meets the requirements. For example, the phase drift amounts of any two nodes are randomly selected to calculate the difference. The maximum difference is then compared with the distribution deviation threshold (e.g., 0.1). If the difference is less than the distribution deviation threshold, the phase drift amounts of each node are relatively balanced, and a second time compensation amount is allocated according to the preset priority and preset compensation weight. The preset priority, preset compensation weight, and distribution deviation threshold can be set as needed.

[0067] In this embodiment, when the device starts up (cold start / restart), steps S1-S2 are executed first to perform the first calibration compensation, realizing segmented hardware compensation; when the device is running normally, step S4 is executed according to the preset compensation cycle to perform the second calibration compensation, realizing full-link segmented dynamic temperature drift compensation and completing real-time temperature drift correction. For example, full-link segmented dynamic temperature drift compensation is performed once every 50ms.

[0068] Furthermore, during normal equipment operation, in addition to temperature drift as the primary factor, other environmental factors may also cause phase errors, such as environmental micro-vibrations. To achieve full coverage of all influencing factors, the phase adaptive dynamic calibration compensation method based on temperature drift compensation provided in this embodiment of the invention further includes obtaining the measured calibration signal of the channel based on the original calibration signal, performing a third calibration compensation, and completing the time-division multiplexing anti-coupling calibration. Specifically, this includes steps S51-S52.

[0069] Step S51: Obtain the channel measured calibration signal based on the original calibration signal, and calculate the measured phase difference based on the channel measured calibration signal.

[0070] Specifically, it includes steps S511-S512.

[0071] Step S511: Obtain the measured calibration signal of the channel based on the original calibration signal.

[0072] The original calibration signal is synchronously distributed to multiple channels to obtain the corresponding channel measured calibration signal, the principle of which is the same as step S13. Furthermore, in order to avoid the impact of the acquisition of channel measured calibration signals on the acquisition of real data, step S511 also includes steps A-B.

[0073] Step A: Identify the acquisition frame status and determine whether the current frame status is within the acquisition frame gap.

[0074] Specifically, before acquiring the channel measured calibration signals of multiple channels, the acquisition frame state corresponding to the channel is first identified. Based on the acquisition frame state, it is determined whether the current frame state is in the acquisition frame gap. This enables the acquisition of channel measured calibration signals only in the acquisition frame gap, without affecting the acquisition of real data and avoiding real data breakpoints.

[0075] For example, in a micro-vibration response signal acquisition sensor, after each frame of real data acquisition is completed, the data is uploaded to the ARM (i.e., real data acquisition and transmission). At this time, the acquisition frame status is marked as idle time, and the current frame status is in the acquisition frame gap. Alternatively, the current frame status can be determined by dual monitoring of "frame synchronization signal + upload status". The FPGA receives the frame synchronization signal (FS) from the AD chip. A high level of FS indicates acquisition in progress, and a low level indicates acquisition completed. An "upload flag" is set: 1 indicates data is being uploaded to the ARM, and 0 indicates upload completed. When FS is low and the upload flag is 0, the current frame status is determined to be in the acquisition frame gap. Any change in the signal status indicates the end of the acquisition frame gap.

[0076] Step B: If it is within the acquisition frame gap, and the gap duration of the acquisition frame gap is not less than the calibration signal acquisition duration, then acquire the channel measured calibration signal according to the original calibration signal.

[0077] If it is in the acquisition frame gap, the gap duration of the acquisition frame gap is further calculated according to the acquisition frame status, and it is determined whether the gap duration is less than the calibration signal acquisition duration, that is, whether the gap duration of the acquisition frame gap is sufficient to complete the acquisition of at least one cycle of channel calibration signal.

[0078] For example, calibration signal acquisition duration In the formula, This represents the analog switch switching time, in this embodiment. ; Indicates a period, analysis frequency The acquisition time of the corresponding channel's measured calibration signal. ; Indicates data transmission time, in this embodiment Interval duration The FPGA's built-in 100MHz timer (10ns resolution) can be used to capture the start and end times of the acquisition frame interval; the difference is the timer value. For example, if the interval duration of the acquisition frame gap is 10μs, and the acquisition duration of the calibration signal for one cycle of the channel measured calibration signal is 7μs, then it is determined that the interval duration of the acquisition frame gap is not less than the acquisition duration of the calibration signal.

[0079] If the data acquisition is in a frame gap, and the gap duration is not less than the calibration signal acquisition duration, then channel calibration signal acquisition is performed. Specifically, the standard signal is synchronously distributed to the analog switch inputs of multiple channels via a power divider. When the current frame state is in a frame gap, the ARM controls the analog switch to switch to the original calibration signal, and the AD chip in the channel synchronously acquires one cycle of the channel's measured calibration signal. After completing one cycle of the channel's measured calibration signal acquisition, the signal is immediately switched back to the real data signal (e.g., the micro-vibration response signal acquired by the sensor), without occupying the real data acquisition time, ensuring that the real data is uninterrupted.

[0080] Understandably, if the data acquisition frame is not in the inter-frame interval, the channel measurement calibration signal will not be acquired.

[0081] Furthermore, if the interval duration is less than the calibration signal acquisition duration, i.e., the idle time of the acquisition frame interval is insufficient to complete one cycle of channel calibration signal, step S511 further includes: Step C: If it is within the acquisition frame gap, and the gap duration of the acquisition frame gap is less than the calibration signal acquisition duration, then a buffer alternation mechanism is used to acquire the channel measured calibration signal.

[0082] If the current frame is within the acquisition frame gap, and the gap duration is less than the calibration signal acquisition duration, then a buffer alternation mechanism is used to acquire the channel measured calibration signal. Specifically, if the current frame state is within the acquisition frame gap, and the gap duration is less than the calibration signal acquisition duration, then the FPGA's built-in dual SRAM (Static Random Access Memory) buffers alternate operation to acquire the channel calibration signal. For example, buffer 1 stores the actual data, and buffer 2 only performs channel measured calibration signal acquisition within the frame gap. The channel measured calibration signal is acquired across frames, and the two are aligned by timestamp through the FPGA's internal synchronization bus to achieve data synchronization and ensure continuous and uninterrupted actual data.

[0083] It should be noted that the analog switch switches the signal path during the frame interval. The original calibration signal enters the channel, and buffer 2 acquires the channel's measured calibration signal. At the end of the acquisition frame interval, it switches to the real data acquisition signal. At this time, buffer 2 has not acquired the channel's measured calibration signal for a complete cycle. It needs to continue acquiring the channel's measured calibration signal in the next acquisition frame interval. By performing channel measured calibration signal acquisition multiple times within the frame interval (i.e., acquiring channel measured calibration signals across frames), a complete cycle of channel measured calibration signal acquisition is completed. The switching time of the analog switch is ≤10ns, much shorter than the interval length (usually...). At high sampling rates, i.e., when the interval duration is short The switching action itself can be considered not to occupy any "real data acquisition time", and is only completed within the interval between acquisition frames, without interrupting the acquisition of real data signals such as vibration sensors.

[0084] It should be noted that both steps B and C can complete the acquisition of channel calibration signals, but step B does not require additional cache resources, does not generate cache latency, and has low requirements for FPGA performance.

[0085] Furthermore, to ensure stable signal transmission, the channel also includes a backup channel, and step S511 further includes: Step D: Detect the signal status of the measured calibration signal of the channel and determine whether the signal status is normal.

[0086] Specifically, the ARM processor monitors the signal status of the measured calibration signal in the channel in real time to determine whether the signal status is normal. For example, the GPIO (General Purpose Input Output) is used to monitor the working status of the current channel (i.e., the main calibration channel, FPGA DDS + main delay line) in real time. If faults such as signal loss, no response from the delay line, or a sudden increase in the measured calibration error of the channel are detected (detection time ≤ 1ms), the signal status is determined to be abnormal, and the channel switching signal is immediately triggered.

[0087] For example, the signal status is determined by a combination of multiple flag bits (e.g., "signal presence flag = 1" = there is a signal, "command receipt signal = 1" = normal response), and there is no single value; among them, "signal loss, no response from delay line, and sudden increase in calibration error" are specific manifestations of abnormal working status. When the flag bit is 0, it corresponds to the corresponding fault. Any fault triggers the main / backup switch of the channel.

[0088] Step E: If the signal state is abnormal, then based on the original calibration signal, obtain the channel measured calibration signal of the multiple backup channels.

[0089] Specifically, if the signal status is abnormal, the channel switching signal is immediately triggered, and the system automatically switches to the backup channel. Based on the original calibration signal, the measured calibration signals of multiple backup channels are obtained. The specific principle is the same as steps A-C, and will not be repeated here.

[0090] Furthermore, the backup channel includes two-stage programmable delay lines, pre-stored with the original calibration signal parameters and the latest phase error model for each analysis frequency. No re-initialization is required after switching, and the calibration interruption time is ≤5ms. After the primary calibration channel fault is cleared, the ARM automatically switches back, simultaneously synchronizing the latest parameters of the primary calibration channel to the backup channel to ensure parameter consistency between the primary and backup channels and maintain redundancy.

[0091] The channel calibration signal is acquired according to step S511. The acquisition period is short (about 0.977ms) and is completed within the frame interval, which meets the requirements of 24-hour continuous acquisition without interrupting the acquisition of real data, and can effectively cope with vibration coupling interference in industrial sites.

[0092] Step S512: Calculate the measured phase difference based on the measured calibration signal of the channel.

[0093] Based on the measured calibration signal of the channel, a 1024-point FFT transformation is used to obtain the corresponding phase value, and then the measured phase difference is calculated. The principle is the same as steps S14-S15. Furthermore, in order to avoid interference from actual vibration coupling on the measured calibration signal of the channel during equipment operation, step S512 also includes steps F-I.

[0094] Step F: Obtain the energy fluctuation of the measured calibration signal of the channel and determine whether the energy fluctuation exceeds the energy fluctuation threshold.

[0095] In this embodiment, the channel measured calibration signal acquired by the AD chip in the channel is transmitted to the FPGA via the LVDS bus, and then transmitted to the DSP chip at high speed via DMA. The DSP chip monitors the energy fluctuation of the channel measured calibration signal in real time and determines whether the energy fluctuation exceeds the energy fluctuation threshold.

[0096] For example, the channel's measured calibration signal is a sine wave signal. The number of data points in each complete cycle of the channel's measured calibration signal is the sampling rate / analysis frequency. The sampling rate is an inherent parameter of the chip that acquires the channel's measured calibration signal, which can be obtained from the product manual or through experimental measurement. Based on the sine wave amplitude of each data point of the channel's measured calibration signal, an amplitude sequence is constructed, and then the energy fluctuation is calculated. Standard energy. , representing the theoretical energy of a 1V standard sine wave, and the measured energy corresponding to the measured calibration signal of the i-th channel. ( (mean of amplitude sequence), energy fluctuation of the i-th channel. .

[0097] Step G: If the energy fluctuation threshold is not exceeded, perform a Fourier transform on the measured calibration signal of the channel to obtain the phase value of each channel.

[0098] If the energy fluctuation does not exceed the energy fluctuation threshold, it indicates that the measured calibration signal of the channel is pure. Therefore, a Fourier transform is performed on the measured calibration signal of the channel to extract the phase value of each channel. In this embodiment, a 1024-point FFT (Fast Fourier Transform) is used to extract the phase value of each channel.

[0099] Step H: If the energy fluctuation threshold is exceeded, the measured calibration signal of the channel is separated, and the separated measured calibration signal of the channel is subjected to Fourier transform to obtain the measured phase value.

[0100] Specifically, if the energy fluctuation exceeds the energy fluctuation threshold, it indicates the presence of real vibration coupling interference. In this case, the channel calibration signal is separated to obtain a pure channel measured calibration signal, and then a Fourier transform is performed to obtain the phase value of each channel.

[0101] In this embodiment, the Recursive Least Squares (RLS) algorithm is used to separate the channel measured calibration signal containing real vibration coupling, extract the pure measured calibration phase value, and ensure that the separation calibration error meets the signal separation threshold requirement, providing a correction benchmark for the measured phase difference. The signal separation threshold requirement is set based on the error range achievable by each calculation and acquisition stage. In this embodiment, the signal separation threshold requirement is less than or equal to 0.08°, where the AD chip phase acquisition error is ≤0.02°, the RLS interference separation error is ≤0.03°, and the multi-channel transmission synchronization error is ≤0.01°. For example, the channel measured calibration signal is a mixed signal. In the formula, This indicates the measured calibration signal of the channel. This represents the channel-pure calibration signal, that is, the pure channel-measured calibration signal obtained after signal separation. Indicates interference signal. Indicates the time step, sets the initial forgetting factor (e.g.) ), initial weight vector (e.g. ), covariance matrix (e.g., , It is the identity matrix. (For large constants, such as 100), perform recursive calculations using the input vector. , Indicates the analysis frequency. The sampling period can be represented by... Determine (wherein) (This represents the number of data points in the measured calibration signal of a complete cycle of the channel). Indicate vector transpose; calculate prediction error Gain vector ,in, Indicates time step Corresponding weight vector transpose, Represents the input vector transpose, Indicates time step Corresponding covariance matrix; update the weight vector based on prediction error and gain vector. Covariance matrix Traverse all data points to determine the channel's pure calibration signal. To achieve and The separation. Among them The optimal weight vector can be the weight vector updated in the last time step, or it can be the mean of all elements of the weight vector. Other optimal solution algorithms are used to determine the optimal weight vector, and no restrictions are imposed here.

[0102] Furthermore, if the separation calibration error does not meet the signal separation threshold requirement, step S4 is triggered to perform a second calibration compensation.

[0103] Step 1: Calculate the measured phase difference based on the measured phase value.

[0104] Based on the measured phase value of each channel, one channel is selected as a reference, and the corresponding measured phase difference for each channel is calculated. For example, the measured phase values ​​of the four channels are as follows: , , , Taking channel 1 as the reference, the corresponding measured phase differences of the four channels are as follows: , , , .

[0105] By monitoring energy fluctuations and performing signal separation, the lack of anti-coupling mechanisms in existing technologies can be compensated for, thereby improving the accuracy of calibration compensation.

[0106] Step S52: Determine the third time compensation amount based on the measured phase difference, and perform the third calibration compensation.

[0107] Based on the measured phase difference, the third time compensation is calculated. Then, using a two-stage programmable delay line configured via the bus, a third calibration compensation is performed on each channel. For example, In the formula, Let be the third time compensation amount for the i-th channel. Let be the measured phase difference of the i-th channel. For frequency analysis.

[0108] Furthermore, in order to improve the long-term stability of the phase compensation model and achieve adaptive device changes (such as device aging), the phase adaptive dynamic calibration compensation method based on temperature drift compensation provided in this embodiment of the invention also includes constructing a phase compensation database and updating the model parameters of the phase compensation model, specifically including steps 61-62.

[0109] Step 61: Construct a phase compensation database based on the measured phase difference, the analysis frequency, the node temperature, and the total phase error.

[0110] Specifically, a phase compensation database is constructed based on the measured phase difference, analysis frequency, node temperature, and total phase error. For example, after the DSP executes steps S4 and S5, it stores the "measured phase error, analysis frequency, node temperature, and total phase error" into Flash memory to form the phase compensation database.

[0111] Step 62: Update the model parameters of the phase compensation model according to the phase compensation database.

[0112] Specifically, based on the measured phase error, analysis frequency, node temperature, and total phase error in the phase compensation database, the model parameters of the phase compensation model are updated, including... and The model parameters can be updated after each new set of data is stored in the phase compensation database, or the model parameters can be updated according to the amount of data; there are no restrictions here.

[0113] For example, when 1000 new data sets are added to the phase compensation database, the DSP uses a least-squares fitting algorithm to update the parameters of the three-dimensional phase error model. and . , In the formula, Indicates analysis frequency The corresponding updated temperature coefficient, Indicates analysis frequency The corresponding temperature coefficient before the update, Indicates analysis frequency The corresponding updated initial phase offset, Indicates analysis frequency The corresponding initial phase offset before the update, Indicates the i-th channel and the analysis frequency. The corresponding measured phase difference, Indicates the i-th channel and the analysis frequency. The corresponding total phase error, Indicates the temperature learning rate. Indicates the phase learning rate. and To ensure smooth parameter updates and avoid accuracy fluctuations caused by abrupt changes, the parameters of the three-dimensional phase error model can also be updated based on the analysis frequency and the measured phase difference. and ,by As the actual phase error and model prediction error ( deviation, , Alternatively, the phase compensation model can be re-established based on the ambient temperature, analysis frequency, and measured phase difference, referring to the process of establishing the phase compensation model in step S3.

[0114] Further, the model parameters are updated according to steps S61-S62. If the update amount of the model parameters exceeds the first update change threshold, for example, a change in b(f) If this occurs, special compensation is triggered, and steps S1-S2 are re-executed to perform segmented hardware compensation.

[0115] Furthermore, an aging warning and calibration frequency adjustment mechanism is set up. If the update amount of the model parameters exceeds the update change threshold (e.g., 0.1), it indicates that the device is severely aging. At this time, an aging warning is issued and the calibration frequency is increased. For example, if the model parameter update amount is ≥0.1° for three consecutive times, the ARM immediately sends a "device aging warning" signal and automatically adjusts the recalibration frequency from 24 hours / time to 12 hours / time to avoid accuracy failure.

[0116] The first calibration compensation is performed according to steps S1-S2 to adapt the device performance, and a phase compensation model is established according to step S3. In step S4, the second time compensation amount is determined through the phase compensation model, and a second calibration compensation is performed to solve the main problem (phase error caused by temperature drift). Then, according to the measured phase difference in steps S51-S52, a third calibration compensation is performed to solve the secondary problem and make up for the remaining phase error. Finally, the model parameters are updated according to the measured phase difference and other data to achieve complementarity and iteration between model prediction and actual verification, realize adaptive device changes (such as device aging), and achieve high-precision, long-term stable phase calibration compensation.

[0117] This invention provides yet another phase adaptive dynamic calibration compensation system based on temperature drift compensation, such as... Figure 2 As shown, it includes: The first compensation module is used to determine a calibration signal based on the analysis frequency, calculate an initial phase difference based on the original calibration signal, and determine a first time compensation amount based on the initial phase difference. The model management module is used to acquire the ambient temperature and establish a phase compensation model based on the ambient temperature, the analysis frequency, and the initial phase difference. The second compensation module is used to obtain the node temperature of the signal transmission link and determine the second time compensation amount using the phase compensation model; wherein, the information transmission link includes multiple signal transmission nodes.

[0118] Furthermore, the phase adaptive dynamic calibration compensation system based on temperature drift compensation also includes: The third supplementary module is used to obtain the measured calibration signal of the channel based on the original calibration signal and perform a third calibration compensation.

[0119] Furthermore, the model management module is also used to build a phase compensation database and update the model parameters of the phase compensation model.

[0120] This invention provides yet another phase adaptive dynamic calibration compensation system based on temperature drift compensation, comprising: 1) Frequency adaptive calibration signal generation module, used to generate a standard sine wave calibration signal (distortion ≤0.01%) with the same frequency as the analysis frequency. It is connected in sequence as FPGA-power divider-analog switch-4-channel AD input terminal; wherein, the power divider adopts AD8001, the analog switch adopts ADG1419, the FPGA adopts XC7A35T, and has a built-in DDS module. 2) The end-to-end temperature monitoring module is used to collect the temperature of four key nodes in the end-to-end process (filter, SHA, AD, FPGA). Four temperature sensors are mounted on the surface of the corresponding devices and connected in the following order: temperature sensor - SPI bus (time-division transmission) - ARM - DSP. The ARM uses STM32H743 and the DSP uses TMS320C6748. The temperature sensor used is ADT7410 with an accuracy of ±0.1℃. 3) Phase error detection module, used to acquire channel calibration signals and channel measured calibration signals, calculate the phase value of each channel and the total phase error superposition value of the whole link, and is connected in the form of 4-channel AD-LVDS bus-FPGA-DMA (direct memory access)-DSP phase calculation unit; among which, the AD adopts a 24-bit dual-core Σ-Δ AD (AD7779). 4) Segmented hardware compensation module, including programmable delay lines, is used to achieve segmented compensation for phase drift across the entire link. It is connected via DSP-SPI bus-first-stage delay line (filter output) and second-stage delay line (AD input). The delay lines use AD9500 with a step size of 1ps. The two programmable delay lines employ segmented independent control and collaborative compensation methods. The first stage corresponds to the waveform recorder output, and the second stage corresponds to the AD input. The DSP issues commands via the SPI bus, supporting single-stage or two-stage collaborative adjustment. Simultaneously, the time adjustment granularity uses a 1ps step size to achieve sub-nanosecond level compensation, adapting to small phase drift in wide-temperature environments. The compensation amount is correlated with the phase drift amount at each node of the entire link, and compensation is based on the mapping relationship between the phase drift amount and the two programmable delay lines, rather than uniform distribution, ensuring targeted compensation.

[0121] 5) Time-division multiplexing control module, used to realize the parallel acquisition of the third calibration compensation and the real data acquisition. The real data acquisition is uninterrupted, according to ARM-GPIO-analog switch-FPGA internal bus, or ARM-GPIO-analog switch-buffer 1 (stores the real acquired data). Buffer 2 (Acquisition of measured calibration signal for execution channel) - FPGA internal synchronization bus; the analog switch uses ADG1419 with a switching time ≤10ns; the buffer uses SRAM. 6) Online self-learning module, which realizes the storage of calibration data, updates of phase error model, and aging of adapter components, and is connected in the following order: DSP (built-in self-learning unit) - internal bus - Flash database (updated model parameters) - SPI bus - delay line control unit; 7) The main and backup redundancy module includes a backup DDS chip and a backup two-stage programmable delay line to achieve seamless switching in case of failure of the main calibration channel and ensure calibration continuity. It is connected in the following order: ARM-GPIO-main / backup switching switch; backup DDS-power divider-analog switch. The fault detection unit monitors the status of the main channel in real time through GPIO. Among them, the backup DDS adopts AD9850 and the backup two-stage programmable delay line adopts AD9500.

[0122] The above-described method and system embodiments are based on the same principles, and their related aspects can be referenced from each other to achieve the same technical effects. For specific implementation processes, please refer to the foregoing embodiments, which will not be repeated here.

[0123] In summary, the phase adaptive dynamic calibration compensation method and system based on temperature drift compensation according to embodiments of the present invention has at least one of the following beneficial effects: 1. By detecting the temperature of all nodes in the entire link and performing two calibration compensations, the influence of different node temperatures on the phase difference is considered, and the response compensation amount is calculated to achieve calibration stability across a wide temperature range and the entire link. At the same time, a phase compensation model is established to facilitate dynamic adjustment of the calibration compensation amount based on changes in analysis frequency and temperature, thereby improving the phase compensation accuracy after device aging and achieving high-precision, long-term stable phase compensation.

[0124] 2. Generate a corresponding calibration signal based on the analysis frequency, and combine it with the phase compensation model to achieve multi-frequency adaptation, effectively solving the error rebound problem in high-frequency scenarios in existing technologies.

[0125] 3. By acquiring the frame status, channel calibration signals are acquired during the frame intervals to avoid interference with the real signal, improve the continuity of the real data, and further perform a third calibration compensation to achieve full coverage of error sources and improve compensation accuracy. Furthermore, by comparing the interval duration of the acquisition frame interval with the calibration signal acquisition duration, in cases where the interval duration of the acquisition frame interval is less than the calibration signal acquisition duration (i.e., the real data is sampled at high frequency and the sampling frame interval is insufficient to complete the acquisition of a standard signal), a buffer alternation mechanism is adopted to acquire the channel calibration signal, enabling parallel execution of calibration and acquisition and solving the problem of real data breakpoints.

[0126] 4. The energy fluctuation of the calibration signal is measured through the detection channel. For fluctuations exceeding the energy fluctuation threshold, the signal is separated and then Fourier transform is performed to reduce the coupling of real vibration to the calibration loop through the mechanical structure in industrial scenarios, thereby improving calibration accuracy.

[0127] Those skilled in the art will understand that all or part of the processes of the methods described in the above embodiments can be implemented by a computer program instructing related hardware, and the program can be stored in a computer-readable storage medium. The computer-readable storage medium may be a disk, optical disk, read-only memory, or random access memory, etc.

[0128] The above description is only a preferred embodiment of the present invention, but the scope of protection of the present invention is not limited thereto. Any changes or substitutions that can be easily conceived by those skilled in the art within the scope of the technology disclosed in the present invention should be included within the scope of protection of the present invention.

Claims

1. A phase adaptive dynamic calibration compensation method based on temperature drift compensation, characterized in that, include: Based on the analysis frequency, the original calibration signal is determined, and the initial phase difference is calculated based on the original calibration signal. Based on the initial phase difference, determine the first time compensation amount and perform the first calibration compensation; Obtain the ambient temperature, and establish a phase compensation model based on the ambient temperature, the analysis frequency, and the initial phase difference; The node temperature of the signal transmission link is obtained, and the second time compensation amount is determined using the phase compensation model to perform a second calibration compensation; wherein, the information transmission link includes multiple signal transmission nodes.

2. The method according to claim 1, characterized in that, Based on the analysis frequency, the original calibration signal is determined, including: Obtain the analysis frequency command and identify the analysis frequency of the micro-vibration acquisition device; Based on the analysis frequency, the original calibration signal is generated by a DDS signal generator; wherein the frequency of the original calibration signal is the same as the upper limit of the analysis frequency.

3. The method according to claim 1, characterized in that, Based on the original calibration signal, the initial phase difference is calculated, including: Based on the original calibration signal, obtain the channel calibration signals for multiple channels; Perform a Fourier transform on the channel calibration signal to obtain the phase value of each channel; Calculate the corresponding initial phase difference based on the phase value of each channel.

4. The method according to claim 1, characterized in that, Obtain the node temperature of the signal transmission link, determine the second compensation value using the phase compensation model, and perform a second calibration compensation, including: Obtain the node temperature of each of the signal transmission nodes; Based on the node temperature and the analysis frequency, the phase drift corresponding to different signal transmission nodes is calculated using the phase compensation model. Determine the total phase error based on all the stated phase drift amounts; Based on the total phase error, a second time compensation amount is determined, and a second calibration compensation is performed.

5. The method according to claim 1, characterized in that, Also includes: Based on the original calibration signal, the measured calibration signal of the channel is obtained, and the measured phase difference is calculated based on the measured calibration signal of the channel. Based on the measured phase difference, the third time compensation amount is determined, and the third calibration compensation is performed.

6. The method according to claim 5, characterized in that, Based on the original calibration signal, the measured calibration signal of the channel is obtained, including: Identify the state of the acquisition frame and determine whether the current frame state is within the acquisition frame gap; If it is within the acquisition frame gap, and the gap duration of the acquisition frame gap is not less than the calibration signal acquisition duration, then the measured calibration signal of the acquisition channel is acquired based on the original calibration signal.

7. The method according to claim 6, characterized in that, Also includes: If the data is within the acquisition frame gap, and the gap duration is less than the calibration signal acquisition duration, then a buffer alternation mechanism is used to acquire the measured calibration signal of the channel.

8. The method according to claim 5, characterized in that, Based on the measured calibration signal of the channel, the measured phase difference is calculated, including: The energy fluctuation of the measured calibration signal of the channel is obtained, and it is determined whether the energy fluctuation exceeds the energy fluctuation threshold. If the energy fluctuation threshold is not exceeded, then the measured calibration signal of the channel is subjected to Fourier transform to obtain the phase value of each channel; If the energy fluctuation threshold is exceeded, the measured calibration signal of the channel is separated, and the separated measured calibration signal of the channel is subjected to Fourier transform to obtain the measured phase value. The measured phase difference is calculated based on the measured phase value.

9. The method according to claim 5, characterized in that, Also includes: A phase compensation database is constructed based on the measured phase difference, the analysis frequency, the node temperature, and the total phase error. The model parameters of the phase compensation model are updated based on the phase compensation database.

10. A phase adaptive dynamic calibration compensation system based on temperature drift compensation, characterized in that, include: The first compensation module is used to determine the calibration signal based on the analysis frequency and calculate the initial phase difference based on the original calibration signal. Based on the initial phase difference, determine the first time compensation amount; The model management module is used to acquire the ambient temperature and establish a phase compensation model based on the ambient temperature, the analysis frequency, and the initial phase difference. The second compensation module is used to obtain the node temperature of the signal transmission link and determine the second time compensation amount using the phase compensation model; wherein, the information transmission link includes multiple signal transmission nodes.

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