Distributor and turnout

Abstract

To provide a distributor capable of obtaining an excellent characteristic in a wide band.SOLUTION: A wilkinson 2 distribution circuit 11 and a high frequency transformer 2 distribution circuit 12 are parallely connected to between an input terminal IN and output terminal outs 1 and 2. The wilkinson 2 distribution circuit is constructed so that a phase of a pass characteristic of a high-pass filter equivalently formed by the wilkinson 2 distribution circuit 11 becomes a delay than a phase of a pass characteristic of a low-pass filter equivalently formed by the high frequency transformer 2 distribution circuit 12. Thus, a phase of the pass characteristic between the low-pass filter and the high-pass filter is matched, and output of the low-pass filter and the high-pass filter is synthesized in a frequency band, and thus, an excellent characteristic can be obtained in a wide band.SELECTED DRAWING: Figure 1

Description

[Technical field]

[0001] The present invention relates to a wideband distributor and splitter for use in a television community viewing system or the like. [Background technology]

[0002] Patent Document 1 discloses a conventional intra-building shared viewing system for a building, an apartment, etc. In the conventional intra-building shared viewing system, a functional block diagram showing the configuration of the intra-building shared viewing system 100 in a case where the building or apartment in which the intra-building shared viewing system 100 is installed has six floors from the first floor to the sixth floor, and each floor has four dwelling units is shown in FIG. A conventional intra-building shared viewing system 100 shown in FIG. 34 is installed in a building such as a building or an apartment building, and is an intra-building shared viewing system in which CATV (cable television) is introduced. In the conventional intra-building shared viewing system 100, a downstream CATV signal transmitted from a CATV station 111a is amplified and transmitted by an amplifier, which is a trunk device 111b inserted in the transmission line, and the downstream CATV signal is branched at a tap-off 111c and drawn into the building via a protector 112. In addition, a BS / CS antenna 113 is installed on the roof of the building, etc. The BS / CS-IF reception signal received by the BS / CS antenna 113 and the downstream CATV signal drawn into the building are mixed by a mixer 114 to become a shared viewing signal, which is transmitted through an intra-building transmission path. The shared viewing signal is amplified by a bidirectional intra-building amplifier 115 and output to a distributor 116. The downstream CATV signal transmitted from the CATV station 111a is a downstream signal in a frequency band of 70 MHz to 962 MHz or 70 MHz to 770 MHz, and the BS·CS-IF received signal is in a frequency band of 1032 MHz to 2610 MHz.

[0003] The intra-building transmission path of the intra-building shared viewing system 100 uses dwelling unit through-wiring, and since the building or apartment in which the intra-building shared viewing system 100 is installed is a six-story building from the first floor to the sixth floor, with four dwelling units on each floor, the serial units 118 installed in each unit are connected in series to adjacent units on upper and lower floors from the sixth floor to the first floor. Since each floor has four dwelling units, the system in which the serial units 118 installed in each unit from the sixth floor to the first floor are connected in series is four systems. Therefore, the signal is divided into four by the distributor 116, and each of the four divided shared viewing signals is transmitted to each of the four systems. The shared signal distributed to the first system is transmitted to six serial units 118-1a, 118-2a, 118-3a, 118-4a, 118-5a, and 118-6a that are installed in each apartment from the sixth floor to the first floor and connected in series. As a result, the shared signal transmitted to the serial units 118-1a to 118-6a is output from the TV terminals of the serial units 118-1a to 118-6a, and the TV signal can be viewed or recorded on a television or recorder connected to the TV terminals via a cable.

[0004] The common signal distributed to the second system is transmitted in the same manner to six serial units 118-1b, 118-2b, 118-3b, 118-4b, 118-5b, and 118-6b that are installed in each apartment from the sixth floor to the first floor and connected in series. As a result, the common signal transmitted to the serial units 118-1b to 118-6b is output from the TV terminals of the serial units 118-1b to 118-6b, making it possible to watch or record the TV signal on a television or recorder connected to the TV terminals via a cable. The common signal distributed to the third system is transmitted in the same manner to six serial units 118-1c, 118-2c, 118-3c, 118-4c, 118-5c, and 118-6c that are installed in each apartment from the sixth floor to the first floor and connected in series. As a result, the common signal transmitted to the serial units 118-1c to 118-6c is output from the TV terminals of the serial units 118-1c to 118-6c, and the TV signal can be viewed or recorded on a television or recorder connected to the TV terminals via a cable. The common signal distributed to the fourth system is transmitted in the same manner to six serial units 118-1d, 118-2d, 118-3d, 118-4d, 118-5d, and 118-6d that are installed in each apartment from the sixth floor to the first floor and connected in series. As a result, the common signal transmitted to the serial units 118-1d to 118-6d is output from the TV terminals of the serial units 118-1d to 118-6d, making it possible to watch or record the TV signal on a television or recorder connected to the TV terminals via a cable. The CATV upstream signal transmitted from each house to the CATV station 111a is 10 MHz to 60 MHz or 10 MHz to 55 MHz, and the in-building shared viewing system 100 supports a frequency band of 10 MHz to 2610 MHz.

[0005] The conventional in-building shared viewing system 100 is a system that supports shared viewing signals up to 2610MHz because the BS / CS-IF reception signal is set to 1032MHz to 2610MHz, and is not compatible with 4K8K broadcasting, which has a frequency band of 1032MHz to 3224MHz for BS / CS-IF reception signals. Therefore, in order to transmit BS / CS left-hand circular polarization IF signals of advanced wideband satellite digital broadcasting in the conventional in-building shared viewing system 100, all of the receiving equipment such as the coaxial cable used as the transmission path, the in-building amplifier, the distributor, the splitter, the serial unit, etc. must be devices capable of transmitting the frequency band of 1032MHz to 3224MHz.

[0006] Here, a distributor using a high-frequency transformer was generally used as the distributor. Figure 35 shows the circuit diagram of a distributor CS using a high-frequency transformer 2-way distributor. The splitter CS shown in Fig. 35 is a two-way splitter, and uses a high-frequency transformer with a ferrite core to achieve a constant impedance over a wide band. That is, the conventional splitter CS is composed of a distribution transformer having a primary coil L1001 and a secondary coil L1002, each of which is made of a ferrite core wound with an insulating coated wire. The distribution transformer acts as an impedance matching transformer, and a signal supplied from the input terminal IN to the primary coil L1001 is output from a tap in the middle of the primary coil L1001 and supplied to the center tap of the secondary coil L1002 for signal distribution. Two distributed signals are output from both ends of the secondary coil L1002, one of the distributed signals is output from the first output terminal OUT1, and the other distributed signal is output from the second output terminal OUT2. A capacitor C connected between the line connecting the tap of the primary coil L1001 and the center tap of the secondary coil L1002 and earth is used for impedance matching, and a resistor R connected between the first output terminal OUT1 and the second output terminal OUT2 is provided for isolation between the first output terminal OUT1 and the second output terminal OUT2. The conventional distributor CS can convert impedance at a constant value in a wide band (especially 10 MHz to 770 MHz) by taking advantage of the characteristics of the ferrite core, which is a magnetic material. In addition, the secondary coil L1002 can ensure a large isolation between the first output terminal OUT1 and the second output terminal OUT2 in a wide band.

[0007] The Wilkinson circuit is also known as a three-terminal high-frequency two-way distributor. A circuit diagram of a distributed constant type Wilkinson circuit 2000 is shown in FIG. As shown in Fig. 36, the Wilkinson circuit 2000 is composed of a distributed constant line W1 connected between the input terminal IN and the first output terminal OUT1, a distributed constant line W2 connected between the input terminal IN and the second output terminal OUT2, and an isolation resistor R connected between the first output terminal OUT1 and the second output terminal OUT2. If the center frequency used in the Wilkinson circuit 2000 is Fo, the electrical lengths of the distributed constant lines W1 and W2 are set to 1 / 4 wavelength of the center frequency used Fo, so that the phase delay amount θo at the center frequency used Fo is 90 degrees. In addition, if the input / output impedance connected to the Wilkinson circuit 2000 is Zo, and the distribution ratio is set to 1:1 for equal distribution, the characteristic impedance Zs of the distributed constant lines W1 and W2 is √2 × Zo. The distributed constant line W1 and the distributed constant line W2 act as a so-called Q matching circuit. If the impedance Zo on the output terminal side is Zs, and the impedance on the input terminal IN side seen through the distributed constant line W1 or W2 is Zx, then according to the operating principle of the Q matching circuit, Zx=Zs 2 / Zo=(√2×Zo) 2 / Zo=2Zo Therefore, the composite impedance seen from the input terminal IN is 1 / 2 the impedance Zo because the impedance Zx of 2Zo is connected in parallel, and matches the impedance Zo of the input terminal IN. The value of the isolation resistor R in the Wilkinson circuit 2000 is set to 2Zo, which provides the maximum isolation between the output terminals in the equal distribution Wilkinson circuit. [Prior art documents] [Patent documents]

[0008] [Patent Document 1] Patent Publication No. 2022-73022 Summary of the Invention [Problem to be solved by the invention]

[0009] When a distributor CS using a high-frequency transformer is used in an in-building shared viewing system 100 compatible with 4K8K broadcasting, it is used in the operating frequency band of 10 MHz to 3224 MHz, which is the frequency band of intermediate frequency signals for CATV, terrestrial digital broadcasting, and BS / CS broadcasting. A distributor CS using a high-frequency transformer can obtain stable performance over a wide frequency band from the low frequency band of 10 MHz, but at frequency bands above 1000 MHz, especially in the high frequency band (2610 MHz to 3224 MHz), the magnetic loss of the ferrite core and the floating capacitance between the windings cannot be ignored, and the distribution loss increases as the frequency increases. Furthermore, when the Wilkinson circuit 2000 is used in the in-building shared viewing system 100 that supports 4K8K broadcasting, it is used in the operating frequency band of 10 MHz to 3224 MHz, which is the frequency band of intermediate frequency signals of CATV, terrestrial digital broadcasting, and BS / CS broadcasting. The Wilkinson circuit 2000 can obtain stable characteristics even at 3224 MHz, but it is considered difficult to obtain good characteristics at 10 MHz, which is considered a low frequency range. Therefore, the present invention aims to provide a distributor and splitter that combines the advantages of a high-frequency transformer distributor and a Wilkinson distributor, and can obtain good characteristics over a wide band that is considered to be at least the usable frequency band of 10 MHz to 3224 MHz. [Means for solving the problem]

[0010] The distributor of the present invention that can achieve the above object is a distributor with a distribution number of 2, in which a high-frequency transformer 2-way distribution circuit and a Wilkinson 2-way distribution circuit are connected in parallel between an input terminal and an output terminal, and the high-frequency transformer 2-way distribution circuit is configured to function equivalently as a low-pass filter between the input terminal and the output terminal, and the Wilkinson 2-way distribution circuit is configured to function equivalently as a high-pass filter between the input terminal and the output terminal, and the Wilkinson 2-way distribution circuit is configured so that the phase of the pass characteristic of the high-pass filter lags behind the phase of the pass characteristic of the low-pass filter. This is a main feature of the distributor in that the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched, the outputs of the low-pass filter and the high-pass filter are frequency band synthesized, and the cutoff frequencies of the low-pass filter and the high-pass filter are approximately the same. The branching device of the present invention that can achieve the above object is a branching device in which a branch transformer branching circuit and a directional coupling line branching circuit are connected in parallel between an input terminal, an output terminal, and a branch terminal, wherein the branch transformer branching circuit comprises a branch transformer that branches a signal, and is circuit-configured to function equivalently as a T-type three-stage low-pass filter between the input terminal, the output terminal, and the branch terminal, and the directional coupling line branching circuit comprises a directional coupling line that branches a signal, and is circuit-configured to function equivalently as a π-type three-stage high-pass filter between the input terminal, the output terminal, and the branch terminal, and the directional coupling line branching circuit is circuit-configured such that the phase of the pass characteristic of the high-pass filter lags behind the phase of the pass characteristic of the low-pass filter, thereby matching the phases of the pass characteristics of the low-pass filter and the high-pass filter, and the outputs of the low-pass filter and the high-pass filter are frequency band-synthesized and output from the output terminal and the branch terminal, and the cut-off frequencies of the low-pass filter and the high-pass filter are approximately the same.

[0011] In the distributor of the present invention described above, when the low-pass filter functions equivalently as a 4n-1 (n=1, 2, 3,...)-stage T-type low-pass filter, the Wilkinson 2-way distributor is configured so that the high-pass filter functions equivalently as a 3-stage π-type high-pass filter, whereby the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched and the frequency bands are combined. Furthermore, in the distributor of the present invention, when the low-pass filter functions equivalently as a 4n+1 (n=1, 2, 3, . . .) stage T-type low-pass filter, the Wilkinson 2-way distributor is configured so that the high-pass filter functions equivalently as a 4n+3 (n=1, 2, 3, . . .) stage π-type high-pass filter, whereby the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched and the frequency bands are combined. Furthermore, in the distributor of the present invention, when the low-pass filter functions equivalently as a 4n+3 (n=1, 2, 3, . . .) stage T-type low-pass filter, the Wilkinson 2-way distributor is configured so that the high-pass filter functions equivalently as a 4n+1 (n=1, 2, 3, . . .) stage π-type high-pass filter, whereby the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched and the frequency bands are combined. Furthermore, in the distributor of the present invention, the high-frequency transformer 2-way distribution circuit distributes the signal into two by a distribution transformer consisting of a primary coil and a secondary coil, and the Wilkinson 2-way distribution circuit is connected to the output terminals via a capacitor that makes the secondary coil less susceptible to the resistance component that functions in the low frequency range. Furthermore, in the distributor of the present invention, a frequency band of 10 MHz to 3224 MHz is obtained as the usable frequency band. Furthermore, in the distributor of the present invention described above, the number of transformer turns is adjusted in the high-frequency transformer 2-way distribution circuit so that the distribution ratio becomes 2:1, and the Wilkinson 2-way distribution circuit is configured so that the distribution ratio becomes 2:1, thereby achieving a distribution ratio of 2:1. Furthermore, a distributor with a distribution number of 2 according to the present invention may be combined with two distributors with a distribution ratio of 2:1 to form a distributor with a distribution number of 3. Furthermore, three distributors with a distribution factor of two according to the present invention may be combined to form a distributor with a distribution factor of four. Furthermore, a distributor with a distribution ratio of 2 according to the present invention may be combined with two distributors with a distribution ratio of 3 to form a distributor with a distribution ratio of 6. Furthermore, a divider with a distribution factor of 2 according to the present invention may be combined with two dividers with a distribution ratio of 4 to form a divider with a distribution factor of 8.

[0012] Another distributor of the present invention that can achieve the above object is a distributor with a distribution number of 2, in which a high-frequency transformer 2-way distribution circuit and a Wilkinson 2-way distribution circuit are connected in parallel between an input terminal and an output terminal, and a predetermined frequency band including an unused frequency band is set as a used frequency band, and the high-frequency transformer 2-way distribution circuit has a circuit configuration that functions equivalently as a low-pass filter between the input terminal and the output terminal, and the Wilkinson 2-way distribution circuit has a circuit configuration that functions equivalently as a high-pass filter between the input terminal and the output terminal, and the cutoff frequency that is approximately the same between the low-pass filter and the high-pass filter is set as a predetermined frequency in the unused frequency band, and the outputs of the low-pass filter and the high-pass filter are frequency band-synthesized when the phases of the pass characteristics of the low-pass filter and the high-pass filter are in a mismatched state. This is a main feature. Effect of the Invention

[0013] The splitter of the present invention is configured to delay the phase of the pass characteristic of the high-pass filter formed by the Wilkinson 2-way splitter with respect to the phase of the pass characteristic of the low-pass filter formed by the high-frequency transformer 2-way splitter, thereby making it possible to match the phase of the pass characteristic when combining frequency bands. This makes it possible to realize a splitter circuit with good splitting performance over a wide frequency band of 10 MHz to 3224 MHz. In addition, the branching device of the present invention is configured to delay the phase of the pass characteristic of the high-pass filter formed by the directional coupling line branching circuit relative to the phase of the pass characteristic of the low-pass filter formed by the branching transformer branching circuit, thereby making it possible to match the phase of the pass characteristic when combining frequency bands. This makes it possible to realize a branching circuit with good branching performance over a wide frequency band from 10 MHz to 3224 MHz. In the splitter and splitter of the present invention, the high-frequency transformer 2-way splitter circuit or the splitter transformer splitter circuit functions equivalently as a low-pass filter, and the Wilkinson 2-way splitter circuit or the directional coupling line splitter circuit functions equivalently as a high-pass filter, so that the low-pass filter and the high-pass filter function as a branching / mixing filter. Furthermore, the circuit is configured to delay the phase of the pass characteristic of the high-pass filter relative to the phase of the pass characteristic of the low-pass filter. This makes it possible to match the phase of the pass characteristic when the frequency bands of the branching / mixing filter are synthesized, and to achieve good division or splitting performance in a wide band. [Brief description of the drawings]

[0014] [Figure 1] 1 is a circuit diagram showing a configuration of a distributor according to a first embodiment of the present invention. [Diagram 2] 4 is a graph showing frequency characteristics of S parameters of the distributor according to the first embodiment of the present invention. [Diagram 3] FIG. 2 is a diagram showing an equivalent circuit diagram of a high-frequency transformer 2-way distribution circuit and a Wilkinson 2-way distribution circuit in the distributor according to the first embodiment of the present invention. [Figure 4] FIG. 2 is a diagram showing an equivalent circuit diagram of a distributor according to the first embodiment of the present invention. [Diagram 5] 1 is a graph showing the phase of the transmission characteristic with respect to frequency in a demultiplexing mixer circuit. [Figure 6] 1 is a graph showing transmission characteristics versus frequency in a branching and mixing circuit. [Figure 7]11 is a graph showing the phase of the pass characteristic versus frequency when the phase of a high-pass filter in a demultiplexing mixer circuit is delayed. [Figure 8] 11 is a graph showing pass characteristics versus frequency when the phase of a high-pass filter in a demultiplexing mixer circuit is delayed. [Figure 9] 4 is a graph showing the phase of the bandpass characteristic versus frequency in an equivalent branching / mixing filter of the distributor according to the first embodiment of the present invention. [Figure 10] 4 is a graph showing the pass characteristic versus frequency in an equivalent branching / mixing filter of the distributor according to the first embodiment of the present invention. [Figure 11] FIG. 11 is a circuit diagram showing the configuration of a distributor according to a second embodiment of the present invention. [Figure 12] 13 is a graph showing frequency characteristics of S parameters of a distributor according to a second embodiment of the present invention. [Figure 13] FIG. 11 is a circuit diagram showing the configuration of a distributor according to a third embodiment of the present invention. [Figure 14] 13 is a graph showing frequency characteristics of S parameters of a distributor according to a third embodiment of the present invention. [Figure 15] FIG. 11 is a circuit diagram showing the configuration of a distributor according to a fourth embodiment of the present invention. [Figure 16] 13 is a graph showing frequency characteristics of S parameters of a distributor according to a fourth embodiment of the present invention. [Figure 17] FIG. 13 is a circuit diagram showing the configuration of a three-way distributor according to a fifth embodiment of the present invention, which is configured by combining distributors according to the embodiments of the present invention. [Figure 18] 18 is a graph showing frequency characteristics of S parameters of the three-way divider according to the fifth embodiment of the present invention shown in FIG. 17. [Figure 19] FIG. 13 is a circuit diagram showing the configuration of a four-way distributor according to a sixth embodiment of the present invention, which is configured by combining distributors according to embodiments of the present invention. [Figure 20] 20 is a graph showing frequency characteristics of S parameters of the four-way divider according to the sixth embodiment of the present invention shown in FIG. 19. [Figure 21] FIG. 13 is a circuit diagram showing the configuration of a 6-way distributor according to a seventh embodiment of the present invention, which is configured by combining distributors according to the embodiments of the present invention. [Figure 22] 22 is a graph showing frequency characteristics of S parameters of the 6-way divider according to the seventh embodiment of the present invention shown in FIG. 21. [Figure 23] FIG. 13 is a circuit diagram showing the configuration of an 8-way distributor according to an eighth embodiment of the present invention, which is configured by combining distributors according to embodiments of the present invention. [Figure 24] 24 is a graph showing frequency characteristics of S parameters of the 8-way divider according to the eighth embodiment of the present invention shown in FIG. 23. [Diagram 25] FIG. 13 is a circuit diagram showing the configuration of a splitter according to a ninth embodiment of the present invention. [Figure 26] 13 is a graph showing frequency characteristics of S parameters of the splitter according to the ninth embodiment of the present invention. [Figure 27] FIG. 19 is a circuit diagram showing the configuration of a distributor according to a tenth embodiment of the present invention. [Figure 28] 23 is a graph showing the frequency characteristics of the pass characteristic of the distributor according to the tenth embodiment of the present invention. [Figure 29] 23 is a graph showing frequency characteristics of S parameters of a distributor according to the tenth embodiment of the present invention. [Diagram 30] 13 is a graph showing frequency characteristics of actual S parameters of a distributor according to a third embodiment of the present invention. [Diagram 31] FIG. 2 is a circuit diagram showing an equivalent circuit of a distribution transformer. [Diagram 32] FIG. 19 is a circuit diagram showing the configuration of a distributor according to an eleventh embodiment of the present invention. [Diagram 33] 23 is a graph showing frequency characteristics of S parameters of a distributor according to the eleventh embodiment of the present invention. [Diagram 34] FIG. 1 is a functional block diagram showing the configuration of a conventional in-building shared viewing system. [Diagram 35] FIG. 2 is a circuit diagram showing a configuration of a high-frequency transformer 2-distribution circuit. [Diagram 36] FIG. 1 is a circuit diagram showing a configuration of a Wilkinson 2-way distributor circuit. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

[0015] <Distributor according to the first embodiment of the present invention> A circuit diagram showing the configuration of a splitter 1 according to a first embodiment of the present invention is shown in Fig. 1. The splitter 1 according to the first embodiment of the present invention shown in Fig. 1 is a wideband splitter 1 with a division ratio of 2, which is composed of a Wilkinson 2-way splitter circuit 11 and a high-frequency transformer 2-way splitter circuit 12. As shown in Fig. 1, the divider 1 with a division number of 2 is a wideband divider 1 with a division ratio of 1:1. In this way, the divider 1 of the first embodiment is an equal divider. The splitter 1 according to the first embodiment of the present invention has an input terminal IN and two output terminals OUT1 and OUT2, which serve as distribution terminals. The input terminal IN and the output terminals OUT1 and OUT2 all have the same impedance Zo, for example, 75Ω. A Wilkinson 2-way distribution circuit 11 and a high-frequency transformer 2-way distribution circuit 12 are connected in parallel between the input terminal IN and the output terminals OUT1 and OUT2. The operating frequency band of the splitter 1 according to the first embodiment of the present invention is at least 10 MHz to 3224 MHz.

[0016] The Wilkinson two-way distribution circuit 11 includes a series circuit of a capacitor C1 connected between the input terminal IN and the first output terminal OUT1, a distributed constant line W1, and a capacitor C2 connected to the first output terminal OUT1, and a series circuit of a distributed constant line W2 connected to a connection point between the other end of the capacitor C1 and one end of the distributed constant line W1, and a capacitor C3 connected to the second output terminal OUT2. The series circuit further includes a resistor R1 connected between the connection point between the other end of the distributed constant line W1 and one end of the capacitor C2 and the connection point between the other end of the distributed constant line W2 and one end of the capacitor C3. The resistor R1 is used for isolation between the output terminals OUT1 and OUT2. In this way, in the Wilkinson 2-way distribution circuit 11, signals that are equally distributed with a distribution ratio of 1:1 are output from the other ends of the distributed constant lines W1, W2, one of the equally distributed distribution signals is output from the first output terminal OUT1, and the other equally distributed distribution signal is output from the second output terminal OUT2. In addition, in the high frequency transformer 2 distribution circuit 12, one end of the inductor L1 is connected to the input terminal IN, and the other end of the primary coil P is connected to the input terminal IN. The distribution transformer T1 is composed of a primary coil P, a ferrite core with an insulating coated wire wound thereon, and a secondary coil S. One end of the secondary coil S is connected to one end of the inductor L2, the other end of which is connected to the first output terminal OUT1, and the other end of the secondary coil S is connected to one end of the inductor L2, the other end of which is connected to the second output terminal OUT2. Furthermore, the tap of the primary coil P and the tap of the secondary coil S are connected, and a capacitor C4 for impedance matching is connected between the connection line and the ground, and a resistor R2 is connected between both ends of the secondary coil S. The resistor R2 is used for isolation between the output terminals OUT1 and OUT2. In this way, in the high frequency transformer 2 distribution circuit 12, signals that are evenly distributed at a distribution ratio of 1:1 are output from both ends of the secondary coil S of the distribution transformer T1, one of the evenly distributed distribution signals is output from the first output terminal OUT1, and the other evenly distributed distribution signal is output from the second output terminal OUT2.

[0017] In the distributor 1 of the first embodiment of the present invention, the high frequency transformer 2 distribution circuit 12 functions as an equivalent T-type three-stage low pass filter by the leakage inductance generated in the distribution transformer T1 and the capacitor C4 as described later, so that the high frequency transformer 2 distribution circuit 12 functions as a low pass filter when combining frequency bands. Inductors L1, L2, and L3 are connected for compensating the leakage inductance value. In addition, the Wilkinson two-way distributor 11 has a circuit configuration that functions equivalently as a high-pass filter, as described later. At the cutoff frequency of this high-pass filter, the distributed constant lines W1 and W2 are regarded as circuit patterns, and since the terminals of the resistor R1 are at the same potential, no current flows between them, and therefore the resistor R1 can be ignored. In addition, since the high-pass filter shares some of the elements that form the low-pass filter, the Wilkinson two-way distributor 11 between the input terminal IN and the first output terminal OUT1 equivalently forms a π-type three-stage high-pass filter by the inductor L1 and leakage inductance, the capacitor C4, the inductor L2 and leakage inductance, and the capacitors C1 and C2, and between the input terminal IN and the second output terminal OUT2 equivalently forms a π-type three-stage high-pass filter by the inductor L1 and leakage inductance, the capacitor C4, the inductor L3 and leakage inductance, and the capacitors C1 and C3.

[0018] In this way, a π-type three-stage high-pass filter is equivalently formed by the Wilkinson two-way distribution circuit 11 in a state where a T-type three-stage low-pass filter is equivalently formed by the high-frequency transformer two-way distribution circuit 12. This makes it possible to delay the phase of the pass characteristic of the high-pass filter relative to the phase of the pass characteristic of the low-pass filter formed by the high-frequency transformer two-way distribution circuit 12, and to match the phase of the pass characteristic when combining frequency bands. The circuit constants are adjusted so that the cutoff frequency of the low-pass filter and the cutoff frequency of the high-pass filter match.

[0019] The frequency characteristics of the S parameters of the splitter 1 according to the first embodiment of the present invention are shown in Fig. 2. The horizontal axis of Fig. 2 represents frequency [GHz], and the vertical axis represents absolute value (magnitude) [dB]. 2, the pass characteristic |S21| between the input terminal IN and the first output terminal OUT1 and the pass characteristic |S31| between the input terminal IN and the second output terminal OUT2 are almost the same frequency characteristic, and are good frequency characteristics that maintain about -3 dB from 10 MHz to 3224 MHz. The reflection characteristic |S11| of the input terminal IN is about -17 dB or less from 10 MHz to 3224 MHz, and the reflection characteristic |S22| of the first output terminal OUT1 and the reflection characteristic |S33| of the second output terminal OUT2 are almost the same frequency characteristic, and are about -16 dB or less from 10 MHz to 3224 MHz, and are good frequency characteristics. Furthermore, the isolation characteristic |S32| between the first output terminal OUT1 and the second output terminal OUT2 is about -15 dB or more from 10 MHz to 3224 MHz, and are good frequency characteristics. In this way, the distributor 1 according to the first embodiment of the present invention operates in a frequency band of at least 10 MHz to 3224 MHz.

[0020] <Equivalent circuit of the distributor according to the first embodiment of the present invention> Here, it will be explained that in the distributor 1 according to the first embodiment of the present invention, the high frequency transformer 2-way distribution circuit 12 functions equivalently as a low pass filter, and the Wilkinson 2-way distribution circuit 11 functions equivalently as a high pass filter. FIG. 3(a) shows a circuit diagram of high frequency transformer 2-way distribution circuit 12, FIG. 3(b) shows an equivalent circuit diagram of high frequency transformer 2-way distribution circuit 12, and FIG. 3(c) shows an equivalent circuit diagram of Wilkinson 2-way distribution circuit 11. The high-frequency transformer 2 distribution circuit 12 shown in Fig. 3(a) is a circuit diagram that takes into consideration the leakage inductance of the distribution transformer T1. That is, the inductor Lo1 between the input terminal IN and one end of the primary coil P of the distribution transformer T1 is an inductor consisting of an inductor L1 and a leakage inductance, the inductor Lo2 between the first output terminal OUT1 and one end of the secondary coil S of the distribution transformer T1 is an inductor consisting of an inductor L2 and a leakage inductance, and the inductor Lo3 between the second output terminal OUT2 and the other end of the secondary coil S of the distribution transformer T1 is an inductor consisting of an inductor L3 and a leakage inductance. Then, the high-frequency transformer 2 distribution circuit 12 functions as a three-stage T-type low-pass filter consisting of a series connection circuit of the inductor Lo1 and the inductor Lo4 connected between the input terminal IN and the output terminal OUT, and a capacitor C4 connected between the connection point between the inductor Lo1 and the inductor Lo4 and the earth, as shown in Fig. 3(b). The low-pass filters formed equivalently between the input terminal IN and the first output terminal OUT1 and between the input terminal IN and the second output terminal OUT2 both have the same circuit configuration as shown in Fig. 3(b). However, in the low-pass filter formed between the input terminal IN and the first output terminal OUT1, the inductor Lo4 becomes the inductor Lo2, and in the low-pass filter formed between the input terminal IN and the second output terminal OUT2, the inductor Lo4 becomes the inductor Lo3.

[0021] In the equivalent circuit of the Wilkinson two-way distribution circuit 11 shown in FIG. 3(c), the Wilkinson two-way distribution circuit 11 functions as a high-pass filter. As described above, the distributed constant lines W1 and W2 are regarded as circuit patterns at the cutoff frequency of this high-pass filter, and since the terminals of the resistor R1 are at the same potential, no current flows between them, and therefore the resistor R1 can be ignored. In addition, since some of the elements of the high-frequency transformer two-way distribution circuit 12 are shared with the high-pass filter, the circuit diagram is designed in consideration of the leakage inductance of the distribution transformer T1. Then, as shown in FIG. 3(c), the Wilkinson two-way distribution circuit 11 is equivalently configured as a circuit including a series connection circuit of inductors Lo1 and Lo4 connected between the input terminal IN and the output terminal OUT, a capacitor C4 connected between the connection point between the inductors Lo1 and Lo4 and the earth, and a capacitor Co connected between the input terminal IN and the output terminal OUT. In this circuit configuration, the operating frequency band of the Wilkinson two-way distribution circuit 11 is approximately 1000 MHz to 3224 MHz, and therefore the capacitor C4 is shorted in this operating frequency band. That is, since the connection point between the inductor Lo1 and the inductor Lo4 is grounded, the Wilkinson 2-way distribution circuit 11 functions as a π-type three-stage high-pass filter as shown in Fig. 3(d). The high-pass filters equivalently formed between the input terminal IN and the first output terminal OUT1 and between the input terminal IN and the second output terminal OUT2 all have the same circuit configuration as shown in Fig. 3(d). However, in the high-pass filter formed between the input terminal IN and the first output terminal OUT1, the inductor Lo4 becomes the inductor Lo2 and the capacitor Co becomes the capacitors C1 and C2, and in the high-pass filter formed between the input terminal IN and the second output terminal OUT2, the inductor Lo4 becomes the inductor Lo3 and the capacitor Co becomes the capacitors C1 and C3.

[0022] From the equivalent circuit diagrams of the high frequency transformer 2-way distribution circuit 12 and the Wilkinson 2-way distribution circuit 11 shown in Fig. 3(b) and (c) described above, the equivalent circuit diagram of the distributor 1 of the first embodiment of the present invention is as shown in Fig. 4(a). In the equivalent circuit diagram shown in Fig. 4(a), the branching / mixing filter 14 is a branching / mixing filter configured by connecting in parallel the equivalent circuits between the input terminal IN and the first output terminal OUT1 of the high frequency transformer 2-way distribution circuit 12 shown in Fig. 3(b) and the Wilkinson 2-way distribution circuit 11 shown in Fig. 3(c), and the branching / mixing filter 15 is a branching / mixing filter configured by connecting in parallel the equivalent circuits between the input terminal IN and the second output terminal OUT2 of the high frequency transformer 2-way distribution circuit 12 shown in Fig. 3(b) and the Wilkinson 2-way distribution circuit 11 shown in Fig. 3(c).

[0023] In the demultiplexer / mixer filters 14 and 15, the operating frequency band of the Wilkinson 2-way distribution circuit 11 is about 1000 MHz to 3224 MHz, so that the capacitor C4 is shorted in this operating frequency band. An equivalent circuit diagram of the demultiplexer / mixer filters 14 and 15 in this case is shown in FIG. 4(b), and the equivalent circuit diagram shown in FIG. 4(b) is a π-type three-stage high-pass filter, which is the same as the equivalent circuit diagram of the Wilkinson 2-way distribution circuit 11 shown in FIG. 3(d). In addition, the operating frequency band of the high-frequency transformer 2-way distribution circuit 12 is about 10 MHz to 1000 MHz, so that the capacitor Co is open in this operating frequency band. An equivalent circuit diagram of the demultiplexer / mixer filters 14 and 15 in this case is shown in FIG. 4(c), and the equivalent circuit diagram shown in FIG. 4(c) is a T-type three-stage low-pass filter, which is the same as the equivalent circuit diagram of the high-frequency transformer 2-way distribution circuit 12 shown in FIG. 3(b).

[0024] That is, in the splitter 1 of the first embodiment of the present invention, the split outputs in which the frequency bands are combined by the demultiplexing / mixing filters 14, 15 of the low-pass filter equivalently formed by the high-frequency transformer 2-way distribution circuit 12 and the high-pass filter equivalently formed by the Wilkinson 2-way distribution circuit 11 are output from the output terminals OUT1, 2. In the splitter 1 of the first embodiment of the present invention, the low-pass filter equivalently formed by the high-frequency transformer 2-way distribution circuit 12 is a T-type three-stage low-pass filter, and the high-pass filter equivalently formed by the Wilkinson 2-way distribution circuit 11 is a π-type three-stage high-pass filter.

[0025] <Phase matching of transmission characteristics> A description will be given of how the distributor 1 of the first embodiment of the present invention can match the phase of the pass characteristic when combining frequency bands without adding a phase correction circuit as in the conventional case. Conventionally, to combine two frequency bands, a branching mixer circuit is used that is configured with a low-pass filter and a high-pass filter that can pass and attenuate each frequency band. In this case, the circuit constants of the Wilkinson 2-way distribution circuit 11 and the high-frequency transformer 2-way distribution circuit 12 are adjusted so that the cutoff frequencies of the low-pass filter and the high-pass filter are the same. The cutoff frequency is set to, for example, 1 GHz. In addition, when combining frequency bands, it is necessary to match the phase of the pass characteristic of each filter at the cutoff frequency. A graph of the phase of the pass characteristic with respect to frequency in the demultiplexing mixer circuit is shown in FIG. 5, and the pass characteristic with respect to frequency in the demultiplexing mixer circuit is shown in FIG. 6. In FIG. 5, the phase of the pass characteristic of the low-pass filter is shown as PL1, the phase of the pass characteristic of the high-pass filter is shown as PH1, and the phase of the demultiplexed and mixed pass characteristic is shown as PD1. In addition, in FIG. 6, the cutoff frequency of the low-pass filter and the high-pass filter is 1 GHz, the pass characteristic of the low-pass filter is shown as SL1, the pass characteristic of the high-pass filter is shown as SH1, and the pass characteristic of the demultiplexed and mixed pass characteristic is shown as SD1. Here, if the phase of the pass characteristic is not matched, a notch characteristic occurs at 1 GHz (cutoff frequency) as shown in FIG. 5 and FIG. 6. To match the phase of the pass characteristic, the phase of the pass characteristic of the high-pass filter is adjusted using a phase correction circuit, so that the phase of the pass characteristic can be matched.

[0026] Referring to FIG. 5, the phase of the high-pass filter is advanced by 90 degrees from the phase of the low-pass filter. The mismatch of the phases between the low-pass filter and the high-pass filter at the cutoff frequency of 1 GHz affects the attenuation of the pass characteristic. Therefore, the phase of the pass characteristic of the high-pass filter is changed by 180 degrees by a phase correction circuit (not shown). FIG. 7 shows a graph of the phase of the pass characteristic with respect to the frequency in the demultiplexing / mixing circuit when the phase of the pass characteristic of the high-pass filter is changed by 180 degrees, and FIG. 8 shows the pass characteristic with respect to the frequency in the demultiplexing / mixing circuit. Referring to FIG. 7, it can be seen that the phase PH1 of the pass characteristic of the high-pass filter lags 90 degrees with respect to the phase PL1 of the pass characteristic of the low-pass filter, and the phase of the phase PD1 of the demultiplexing / mixing pass characteristic is matched. Also, referring to FIG. 8, it can be seen that the cutoff frequency of the low-pass filter and the high-pass filter is set to 1 GHz, and no notch characteristic occurs at 1 GHz in the demultiplexing / mixing pass characteristic SD1. This is because the phase of the phase PD1 of the demultiplexing / mixing pass characteristic is matched. Thus, in the conventional demultiplexing / mixing circuit, a phase correction circuit is added to match the phase of the pass characteristic of the cutoff frequency, thereby synthesizing the frequency bands.

[0027] As explained above, in a demultiplexing mixer circuit, if the phase of the high-pass filter's pass characteristic is advanced relative to the phase of the low-pass filter's pass characteristic at the cutoff frequency of the low-pass filter and high-pass filter, the pass characteristics are mismatched, and if it is delayed, the pass characteristics are matched. The phase changes by 90 degrees for each element that makes up the filter. In the branching / mixing filters 14 and 15 of the distributor 1 according to the first embodiment of the present invention, the circuit configuration of the high-pass filter equivalently formed by the Wilkinson 2-way distribution circuit 11 is affected by the inductors Lo1 and Lo4 of the high-frequency transformer 2-way distribution circuit 12 as described above, and is therefore equivalently regarded as a π-type three-stage high-pass filter as shown in FIG. 3(d). As described above, the number of elements of the high-pass filter equivalently formed by the Wilkinson 2-way distribution circuit 11 is three, so the phase change is 3×90 degrees=270 degrees=−90 degrees. Therefore, there is a delay of 90 degrees, and the phase of the pass characteristic of the high-pass filter is matched without using a phase correction circuit. A graph of the phase of the pass characteristic versus frequency in the branching / mixing filters 14 and 15 of the distributor 1 according to the first embodiment of the present invention is shown in FIG. 9, and the pass characteristic versus frequency in the branching / mixing filters 14 and 15 is shown in FIG. 10. 9, it can be seen that the phase PH1 of the pass characteristic of the high-pass filter lags 90 degrees behind the phase PL1 of the pass characteristic of the low-pass filter, and the phase of the pass characteristic PD1 resulting from the demultiplexing and mixing is matched. Also, referring to FIG 10, it can be seen that the cutoff frequency of the low-pass filter and the high-pass filter is set to 1 GHz, and no notch characteristic occurs at 1 GHz in the pass characteristic SD1 resulting from the demultiplexing and mixing. This is because the phase of the pass characteristic PD1 resulting from the demultiplexing and mixing is matched. In this way, in the branching / mixing filters 14 and 15 of the distributor 1 according to the first embodiment of the present invention, the phases of the pass characteristics of the cutoff frequencies are matched and the frequency bands are combined without adding a phase correction circuit.

[0028] <Distributor according to the second embodiment of the present invention> A circuit diagram showing the configuration of a splitter 2 according to a second embodiment of the present invention is shown in Fig. 11. The splitter 2 according to the second embodiment of the present invention shown in Fig. 11 is a wideband splitter 2 having a split ratio of 1:1 and a split number of 2, which is composed of a Wilkinson 2-way splitter circuit 21 and a high-frequency transformer 2-way splitter circuit 12. In this way, the splitter 2 according to the second embodiment is an equal splitter. This is a wideband distributor 2 with a distribution factor of 2. As shown in Fig. 11, the distributor 2 with a division ratio of 2 includes an input terminal IN and two output terminals OUT1 and OUT2, and the output terminals OUT1 and OUT2 are used as distribution terminals. The input terminal IN and the output terminals OUT1 and OUT2 all have the same impedance Zo, for example, 75Ω. A Wilkinson 2-way distribution circuit 21 and a high-frequency transformer 2-way distribution circuit 12 are connected in parallel between the input terminal IN and the output terminals OUT1 and OUT2. The operating frequency band of the distributor 2 of the second embodiment of the present invention is at least 10MHz to 3224MHz.

[0029] The Wilkinson 2-way distribution circuit 21 is configured by connecting a capacitor C5 between the input terminal IN and one end of the distributed constant line W2 in the Wilkinson 2-way distribution circuit 11 of the distributor 1 of the first embodiment, and connecting a series circuit of a resistor R3 and an inductor L4 between one end of the distributed constant line W1 and one end of the distributed constant line W2. In the Wilkinson 2-way distribution circuit 21, the capacitors C1 and C5 are used as the first stage circuit of the Wilkinson 2-way distribution circuit 21, a two-way distribution circuit using the distributed constant lines W1 and W2 is connected to the latter stage, and a series circuit of a resistor R3 and an inductor L4 is connected between the stages for matching, thereby forming a multi-stage circuit configuration of the Wilkinson 2-way distribution circuit 21. That is, a series circuit of a capacitor C1, one end of which is connected to the input terminal IN, a distributed constant line W1, and a capacitor C2, the other end of which is connected to the first output terminal OUT1, is connected between the input terminal IN and the first output terminal OUT1. Also, a series circuit of a capacitor C5, one end of which is connected to the input terminal IN, a distributed constant line W2, and a capacitor C3, the other end of which is connected to the second output terminal OUT2, is connected between the input terminal IN and the second output terminal OUT2. Furthermore, a series circuit of a resistor R3 and an inductor L4 is connected between the connection point between the other end of the capacitor C1 and one end of the distributed constant line W1 and the connection point between the other end of the capacitor C5 and one end of the distributed constant line W2. Furthermore, a resistor R1 is connected between the other end of the distributed constant line W1 and the other end of the distributed constant line W2. The resistor R1 is used for isolation between the output terminals OUT1 and OUT2. In this way, in the Wilkinson 2-way distribution circuit 21, signals equally distributed with a distribution ratio of 1:1 are output from the other ends of the distributed constant lines W1 and W2, one equally distributed distribution signal is output from the first output terminal OUT1, and the other equally distributed distribution signal is output from the second output terminal OUT2. Moreover, since the high frequency transformer 2 distribution circuit 12 has the same configuration as the high frequency transformer 2 distribution circuit 12 in the distributor 1 of the first embodiment, a description thereof will be omitted; however, in the high frequency transformer 2 distribution circuit 12, signals that are evenly distributed at a distribution ratio of 1:1 are output from both ends of the secondary coil S of the distribution transformer T1, one of the evenly distributed distribution signals is output from the first output terminal OUT1, and the other evenly distributed distribution signal is output from the second output terminal OUT2.

[0030] In the distributor 2 of the second embodiment of the present invention, the high frequency transformer 2 distribution circuit 12 functions as an equivalent T-type three-stage low pass filter by the leakage inductance generated in the distribution transformer T1 and the capacitor C4 as described above, so that the high frequency transformer 2 distribution circuit 12 functions as a low pass filter when combining frequency bands. Inductors L1, L2, and L3 are connected for compensating for the leakage inductance value. The Wilkinson 2-way splitter 21 is configured to function equivalently as a high-pass filter, similar to the Wilkinson 2-way splitter 11 in the splitter 1 of the first embodiment. The distributed constant lines W1 and W2 at the cutoff frequency of the equivalently formed high-pass filter are regarded as a circuit pattern, and both ends of the series circuit of the resistor R3 and the inductor L4 are at the same potential, and the terminals of the resistor R1 are also at the same potential, so no current flows, and therefore the resistor R3, the inductor L4, and the resistor R1 can be ignored. Furthermore, because the high-pass filter shares some of the elements that form the low-pass filter, in the Wilkinson 2-way distribution circuit 21 between the input terminal IN and the first output terminal OUT1, a π-type three-stage high-pass filter shown in FIG. 3(d) is equivalently formed by inductor L1 and the leakage inductance, capacitor C4, inductor L2 and the leakage inductance, and capacitors C1 and C2, and between the input terminal IN and the second output terminal OUT2, a π-type three-stage high-pass filter shown in FIG. 3(d) is equivalently formed by inductor L1 and the leakage inductance, capacitor C4, inductor L3 and the leakage inductance, and capacitors C5 and C3.

[0031] In this manner, in a state where a T-type three-stage low-pass filter is equivalently formed by the high-frequency transformer two-way distribution circuit 12, a π-type three-stage high-pass filter is equivalently formed by the Wilkinson two-way distribution circuit 21. As a result, as described above, the phase of the pass characteristic of the high-pass filter formed by the Wilkinson two-way distribution circuit 21 can be delayed relative to the phase of the pass characteristic of the low-pass filter formed by the high-frequency transformer two-way distribution circuit 12, and the phase of the pass characteristic can be matched when frequency bands are synthesized in a demultiplexing / mixing filter composed of the low-pass filter and the high-pass filter. The circuit constants are adjusted so that the cutoff frequency of the low-pass filter and the cutoff frequency of the high-pass filter coincide with each other.

[0032] The frequency characteristics of the S parameters of the splitter 2 according to the second embodiment of the present invention are shown in Fig. 12. The horizontal axis of Fig. 12 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 12, the pass characteristic |S21| between the input terminal IN and the first output terminal OUT1 and the pass characteristic |S31| between the input terminal IN and the second output terminal OUT2 are almost the same frequency characteristic, and are good frequency characteristics that maintain about -3 dB from 10 MHz to 3224 MHz. The reflection characteristic |S11| of the input terminal IN is about -20 dB or less from 10 MHz to 3224 MHz, and the reflection characteristic |S22| of the first output terminal OUT1 and the reflection characteristic |S33| of the second output terminal OUT2 are almost the same frequency characteristic, and are about -21 dB or less from 10 MHz to 3224 MHz, and are good frequency characteristics. Furthermore, the isolation characteristic |S32| between the first output terminal OUT1 and the second output terminal OUT2 is about -21 dB or more from 10 MHz to 3224 MHz, and are good frequency characteristics. In addition, in the distributor 2 of the second embodiment, the Wilkinson 2-way distributor 21 has a multi-stage circuit configuration to achieve a wider bandwidth, and therefore the distribution characteristics are improved compared to the distributor 1 of the first embodiment, as shown in Figure 12. In this way, the distributor 2 in the second embodiment of the present invention operates in a frequency band of at least 10 MHz to 3224 MHz.

[0033] The equivalent circuit of the splitter 2 of the second embodiment of the present invention is also the equivalent circuit shown in Fig. 4(a) described above. As described above, the equivalent circuit shown in Fig. 4(a) is composed of a demultiplexing / mixing filter 14 configured by connecting in parallel a low-pass filter formed by the high-frequency transformer 2-way distribution circuit 12 and a high-pass filter formed by the Wilkinson 2-way distribution circuit 21 between the input terminal IN and the first output terminal OUT1, and a demultiplexing / mixing filter 15 configured by connecting in parallel a low-pass filter formed by the high-frequency transformer 2-way distribution circuit 12 and a high-pass filter formed by the Wilkinson 2-way distribution circuit 21 between the input terminal IN and the second output terminal OUT2. In this case, the circuit constants of the Wilkinson 2-way distribution circuit 21 and the high-frequency transformer 2-way distribution circuit 12 are adjusted so that the cutoff frequencies of the low-pass filter and the high-pass filter coincide with each other. The cutoff frequency is set to, for example, 1 GHz.

[0034] In the branching / mixing filters 14 and 15, since the operating frequency band of the Wilkinson 2-way distribution circuit 21 is approximately 1000 MHz to 3224 MHz, the equivalent circuit of the branching / mixing filters 14 and 15 has the circuit configuration shown in Fig. 4(b) described above, and is a π-type three-stage high-pass filter. Also, since the operating frequency band of the high-frequency transformer 2-way distribution circuit 12 is approximately 10 MHz to 1000 MHz, the equivalent circuit of the branching / mixing filters 14 and 15 has the circuit configuration shown in Fig. 4(c) described above, and is a T-type three-stage low-pass filter. As a result, the phase of the pass characteristic of the high-pass filter formed by Wilkinson 21 lags behind the phase of the pass characteristic of the low-pass filter formed by high-frequency transformer 2-way distribution circuit 12 by 90 degrees, and the phases of the pass characteristics demultiplexed and mixed in the demultiplexing and mixing filters 14, 15 are matched. In this way, in the branching / mixing filters 14 and 15 of the distributor 2 according to the second embodiment of the present invention, the phases of the pass characteristics of the cutoff frequencies are matched and the frequency bands are combined without adding a phase correction circuit.

[0035] <Distributor according to the third embodiment of the present invention> A circuit diagram showing the configuration of a splitter 3 according to a third embodiment of the present invention is shown in Fig. 13. The splitter 3 according to the third embodiment of the present invention shown in Fig. 13 is a wideband splitter 3 having a split number of 2 and a split ratio of 1:1, which is composed of a Wilkinson 2-way splitter circuit 31 and a high-frequency transformer 2-way splitter circuit 32. In this way, the splitter 3 according to the third embodiment is an equal splitter. As shown in Fig. 13, the distributor 3 with a division factor of 2 includes an input terminal IN and two output terminals OUT1 and OUT2, and the output terminals OUT1 and OUT2 are used as distribution terminals. The input terminal IN and the output terminals OUT1 and OUT2 all have the same impedance Zo, for example, 75Ω. A Wilkinson 2-way distribution circuit 31 and a high-frequency transformer 2-way distribution circuit 32 are connected in parallel between the input terminal IN and the output terminals OUT1 and OUT2. The operating frequency band of the distributor 3 of the third embodiment of the present invention is at least 10MHz to 3224MHz.

[0036] The Wilkinson two-way distribution circuit 31 is obtained by eliminating the capacitors C2 and C3 in the Wilkinson two-way distribution circuit 21 of the divider 2 of the second embodiment. In addition, one end of the capacitor C6 is connected to the other end of the resistor R1, and the other end is connected to the other end of the distributed constant line W2. In the Wilkinson two-way distribution circuit 31, the output-side capacitors C2 and C3 are eliminated, and the distributed constant lines W1 and W2 in the rear stage of the Wilkinson two-way distribution circuit 31 are used as one of the matching elements to function as a two-way distribution circuit by a matching circuit combined with the inductors L2 and L3 in the high-frequency transformer two-way distribution circuit 32. In addition, one end of the matching capacitor C6 is connected to the other end of the resistor R1. Furthermore, the matching resistor R2 is eliminated in the high-frequency transformer two-way distribution circuit 32, and the circuit configuration is such that the matching resistor R3 in the first stage of the Wilkinson two-way distribution circuit 31 is shared. That is, a series circuit of a capacitor C1, one end of which is connected to the input terminal IN, and a distributed constant line W1, the other end of which is connected to the first output terminal OUT1, is connected between the input terminal IN and the first output terminal OUT1. Also, a series circuit of a capacitor C5, one end of which is connected to the input terminal IN, and a distributed constant line W2, the other end of which is connected to the second output terminal OUT2, is connected between the input terminal IN and the second output terminal OUT2. Furthermore, a series circuit of a resistor R3 and an inductor L4 is connected between the connection point between the other end of the capacitor C1 and one end of the distributed constant line W1 and the connection point between the other end of the capacitor C5 and one end of the distributed constant line W2. Furthermore, a series circuit of a resistor R1 and a capacitor C6 is connected between the other end of the distributed constant line W1 and the other end of the distributed constant line W2. The resistor R1 is used for isolation between the output terminals OUT1 and OUT2. In this way, in the Wilkinson 2-way distribution circuit 31, signals that are equally distributed with a distribution ratio of 1:1 are output from the other ends of the distributed constant lines W1, W2, one of the equally distributed distribution signals is output from the first output terminal OUT1, and the other equally distributed distribution signal is output from the second output terminal OUT2. Also, the high frequency transformer 2 distribution circuit 32 is configured by omitting the resistor R2 in the high frequency transformer 2 distribution circuit 12 in the distributor 1 of the first embodiment, but performs the same function as the high frequency transformer 2 distribution circuit 12. That is, in the high frequency transformer 2 distribution circuit 32, signals equally distributed at a distribution ratio of 1:1 are output from both ends of the secondary coil S of the distribution transformer T1, one of the equally distributed distribution signals is output from the first output terminal OUT1, and the other equally distributed distribution signal is output from the second output terminal OUT2.

[0037] In the distributor 3 of the third embodiment of the present invention, the high frequency transformer 2 distribution circuit 32 functions as an equivalent T-type three-stage low pass filter by the leakage inductance generated in the distribution transformer T1 and the capacitor C4, so that the high frequency transformer 2 distribution circuit 32 functions as a low pass filter when combining frequency bands. Inductors L1, L2, and L3 are connected for compensating for the leakage inductance value. The Wilkinson 2-way splitter 31 is configured to function equivalently as a high-pass filter, similar to the Wilkinson 2-way splitter 21 in the splitter 2 of the second embodiment. The distributed constant lines W1 and W2 at the cutoff frequency of the equivalently formed high-pass filter are regarded as a circuit pattern, and both ends of the series circuit of resistor R3 and inductor L4 are at the same potential, and both ends of the series circuit of resistor R1 and capacitor C6 are also at the same potential, so that no current flows, and therefore resistor R3, inductor L4, resistor R1, and capacitor C6 can be ignored. In addition, because the high-pass filter shares some of the elements that form the low-pass filter, in the Wilkinson 2-way distribution circuit 31 between the input terminal IN and the first output terminal OUT1, a π-type three-stage high-pass filter shown in FIG. 3(d) is equivalently formed by inductor L1 and the leakage inductance, capacitor C4, inductor L2 and the leakage inductance, and capacitor C1, and between the input terminal IN and the second output terminal OUT2, a π-type three-stage high-pass filter shown in FIG. 3(d) is equivalently formed by inductor L1 and the leakage inductance, capacitor C4, inductor L3 and the leakage inductance, and capacitor C5.

[0038] In this manner, in a state where a T-type three-stage low-pass filter is equivalently formed by the high-frequency transformer two-way distribution circuit 32, a π-type three-stage high-pass filter is equivalently formed by the Wilkinson two-way distribution circuit 31. As a result, as described above, the phase of the pass characteristic of the high-pass filter formed by the Wilkinson two-way distribution circuit 31 can be delayed relative to the phase of the pass characteristic of the low-pass filter formed by the high-frequency transformer two-way distribution circuit 32, and the phase of the pass characteristic can be matched when frequency bands are synthesized in a demultiplexing / mixing filter composed of the low-pass filter and the high-pass filter. The circuit constants are adjusted so that the cutoff frequency of the low-pass filter and the cutoff frequency of the high-pass filter coincide with each other.

[0039] The frequency characteristics of the S parameters of the splitter 3 according to the third embodiment of the present invention are shown in Fig. 14. The horizontal axis of Fig. 14 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 14, the pass characteristic |S21| between the input terminal IN and the first output terminal OUT1 and the pass characteristic |S31| between the input terminal IN and the second output terminal OUT2 are almost the same frequency characteristic, and are good frequency characteristics that maintain about -3 dB from 10 MHz to 3224 MHz. The reflection characteristic |S11| of the input terminal IN is about -30 dB or less from 10 MHz to 3224 MHz, and the reflection characteristic |S22| of the first output terminal OUT1 and the reflection characteristic |S33| of the second output terminal OUT2 are almost the same frequency characteristic, and are about -35 dB or less from 10 MHz to 3224 MHz, and are good frequency characteristics. Furthermore, the isolation characteristic |S32| between the first output terminal OUT1 and the second output terminal OUT2 is about -31 dB or more from 10 MHz to 3224 MHz, and are good frequency characteristics. In the divider 3 of the third embodiment, the impedance conversion is subdivided in the matching circuit between the distributed constant lines W1, W2 and the inductors L2, L3 in the rear stage of the Wilkinson 2-way divider circuit 31, and as a result, the division performance is improved compared to the divider 2 of the second embodiment, as shown in Fig. 14. Also, by subdividing the impedance conversion in the rear stage of the Wilkinson 2-way divider circuit 31, the line length of the distributed constant lines W1, W2 can be shortened to about 2 / 3 compared to a 2-way divider circuit that uses impedance conversion by a 1 / 4 wavelength transformer of a microstrip line, and the circuit mounting area can be reduced. In this way, the distributor 3 of the third embodiment of the present invention is designed to operate in a frequency band of at least 10 MHz to 3224 MHz.

[0040] The equivalent circuit of the splitter 3 of the third embodiment of the present invention is also the equivalent circuit shown in Fig. 4(a) described above. As described above, the equivalent circuit shown in Fig. 4(a) is composed of a demultiplexing / mixing filter 14 configured by connecting in parallel a low-pass filter formed by the high-frequency transformer 2-way distribution circuit 32 and a high-pass filter formed by the Wilkinson 2-way distribution circuit 31 between the input terminal IN and the first output terminal OUT1, and a demultiplexing / mixing filter 15 configured by connecting in parallel a low-pass filter formed by the high-frequency transformer 2-way distribution circuit 32 and a high-pass filter formed by the Wilkinson 2-way distribution circuit 31 between the input terminal IN and the second output terminal OUT2. In this case, the circuit constants of the Wilkinson 2-way distribution circuit 31 and the high-frequency transformer 2-way distribution circuit 32 are adjusted so that the cutoff frequencies of the low-pass filter and the high-pass filter coincide with each other. The cutoff frequency is set to, for example, 1 GHz.

[0041] In the demultiplexing / mixing filters 14 and 15, the usable frequency band of the Wilkinson 2-way distribution circuit 31 is approximately 1000 MHz to 3224 MHz, so the equivalent circuit of the demultiplexing / mixing filters 14 and 15 has the circuit configuration shown in Fig. 4(b) described above, and is a π-type 3-stage high-pass filter. Also, the usable frequency band of the high-frequency transformer 2-way distribution circuit 32 is approximately 10 MHz to 1000 MHz, so the equivalent circuit of the demultiplexing / mixing filters 14 and 15 has the circuit configuration shown in Fig. 4(c) described above, and is a T-type 3-stage low-pass filter. As a result, the phase of the pass characteristic of the high-pass filter formed by Wilkinson 2-way distribution circuit 31 lags behind the phase of the pass characteristic of the low-pass filter formed by high-frequency transformer 2-way distribution circuit 32 by 90 degrees, and the phases of the pass characteristics demultiplexed and mixed in the demultiplexing and mixing filters 14, 15 are matched. In this way, in the branching / mixing filters 14 and 15 of the distributor 3 according to the third embodiment of the present invention, the phases of the pass characteristics of the cutoff frequencies are matched and the frequency bands are combined without adding a phase correction circuit.

[0042] <Conditions for matching the phases of distributors 1 to 3 according to the first to third embodiments of the present invention> In the distributors 1 to 3 of the first to third embodiments of the present invention described above, the circuit is configured to delay the phase of the pass characteristic of the high-pass filter formed by the Wilkinson two-way distribution circuits 11 to 31 relative to the phase of the pass characteristic of the low-pass filter formed by the high-frequency transformer two-way distribution circuits 12 and 32, and thereby the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched and the frequency band is synthesized. In this case, it is considered to make the Wilkinson two-way distribution circuits 11 to 31 multi-staged to widen the band. When the Wilkinson two-way distribution circuits 11 to 31 are multi-staged, if the low-pass filter formed by the high-frequency transformer two-way distribution circuits 12 and 32 functions equivalently as a 4n-1 (n=1, 2, 3, . . .)-stage T-type low-pass filter, the Wilkinson two-way distribution circuits 11 to 31 are configured so that the high-pass filter formed by the Wilkinson two-way distribution circuits 11 to 31 functions equivalently as a three-stage π-type high-pass filter. As a result, the phase of the pass characteristic of the high-pass filter lags behind the phase of the pass characteristic of the low-pass filter, so that the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched and the frequency bands are synthesized.

[0043] Furthermore, when the low-pass filter functions equivalently as a 4n+1 (n=1, 2, 3...) stage T-type low-pass filter, the Wilkinson 2-way distributors 11-31 are configured so that the high-pass filter functions equivalently as a 4n+3 (n=1, 2, 3...) stage π-type high-pass filter. As a result, the phase of the pass characteristic of the high-pass filter lags behind the phase of the pass characteristic of the low-pass filter, and the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched to synthesize the frequency bands. Furthermore, when the low-pass filter functions equivalently as a 4n+3 (n=1, 2, 3...) stage T-type low-pass filter, the Wilkinson 2-way distributors 11-31 are configured so that the high-pass filter functions equivalently as a 4n+1 (n=1, 2, 3...) stage π-type high-pass filter. As a result, the phase of the pass characteristic of the high-pass filter lags behind the phase of the pass characteristic of the low-pass filter, and the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched to synthesize the frequency bands.

[0044] <Distributor according to the fourth embodiment of the present invention> A circuit diagram showing the configuration of a splitter 4 according to a fourth embodiment of the present invention is shown in Fig. 15. The splitter 4 according to the fourth embodiment of the present invention shown in Fig. 15 is a wideband splitter 4 with a split ratio of 2:1, which is composed of a Wilkinson 2-way splitter circuit 41 and a high-frequency transformer 2-way splitter circuit 42. In this way, the splitter 4 according to the fourth embodiment is an unequal splitter. As shown in FIG. 15, the distributor 4 with a distribution ratio of 2:1 includes an input terminal IN and two output terminals OUT1 and OUT2, and the first output terminal OUT1 is a distribution terminal that outputs 1 / 3 of the signal power and the second output terminal OUT2 is a distribution terminal that outputs 2 / 3 of the signal power. The impedance of the first output terminal OUT1 is 2Zo, and the input terminal IN and the second output terminal OUT2 are impedance Zo. Zo is set to, for example, 75Ω. Between the input terminal IN and the output terminals OUT1 and OUT2, a Wilkinson 2-way distribution circuit 41 and a high-frequency transformer 2-way distribution circuit 42 are connected in parallel. The frequency band used by the distributor 4 with a distribution ratio of 2:1 according to the fourth embodiment of the present invention is at least 10MHz to 3224MHz.

[0045] In the Wilkinson 2-way distribution circuit 41, the distributed constant line W1 is a distributed constant line W3 with an impedance of 2Zo, and the distributed constant line W2 is a distributed constant line W4 with an impedance Zo of 1 / 2 that of the distributed constant line W3 in the Wilkinson 2-way distribution circuit 31 of the third embodiment. The other end of the inductor L5 is connected to one end of the resistor R3, and one end of the inductor L5 is connected to one end of the distributed constant line W1, and the other end of the capacitor C7 is connected to one end of the resistor R1, and one end of the capacitor C7 is connected to the other end of the distributed constant line W1. Here, the matching inductor L5 corresponding to the input side capacitor C1 and the matching inductor L4 corresponding to the capacitor C5 are connected to both sides of the resistor R3, and the matching capacitor C7 corresponding to the output side inductor L2 of the high frequency transformer 2-way distribution circuit 42 and the matching capacitor C6 corresponding to the inductor L3 are connected to both sides of the resistor R1. That is, a series circuit of a capacitor C1, one end of which is connected to the input terminal IN, and a distributed constant line W3, the other end of which is connected to the first output terminal OUT1, is connected between the input terminal IN and the first output terminal OUT1. Also, a series circuit of a capacitor C5, one end of which is connected to the input terminal IN, and a distributed constant line W4, the other end of which is connected to the second output terminal OUT2, is connected between the input terminal IN and the second output terminal OUT2. Furthermore, a series circuit of an inductor L5, a resistor R3, and an inductor L4 is connected between a connection point between the other end of the capacitor C1 and one end of the distributed constant line W3 and a connection point between the other end of the capacitor C5 and one end of the distributed constant line W4. Furthermore, a series circuit of a capacitor C7, a resistor R1, and a capacitor C6 is connected between the other end of the distributed constant line W2 and the other end of the distributed constant line W4. The resistor R1 is used for isolation between the output terminals OUT1 and OUT2. In the Wilkinson 2-way distribution circuit 41, by adjusting the circuit constants, unequally distributed signals with a distribution ratio of 2:1 are output from the other ends of the distributed constant lines W3 and W4, respectively, a distributed signal with 1 / 3 of the signal power is output from the first output terminal OUT1, and a distributed signal with 2 / 3 of the signal power is output from the second output terminal OUT2. In addition, in the high frequency transformer 2 distribution circuit 32 in the distributor 3 of the third embodiment, the transformer turns ratio of the distribution transformer T2 is adjusted so that the power distribution ratio is 2:1. In the high frequency transformer 2 distribution circuit 42, signals that are unequally distributed with a distribution ratio of 2:1 are output from both ends of the secondary coil S of the distribution transformer T2, a distribution signal of 1 / 3 of the signal power is output from the first output terminal OUT1, and a distribution signal of 2 / 3 of the signal power is output from the second output terminal OUT2.

[0046] In the distributor 4 of the fourth embodiment of the present invention, the high frequency transformer 2 distribution circuit 42 functions as an equivalent T-type three-stage low pass filter by the leakage inductance generated in the distribution transformer T1 and the capacitor C4, so that the high frequency transformer 2 distribution circuit 42 functions as a low pass filter when combining frequency bands. Inductors L1, L2, and L3 are connected for compensating for the leakage inductance value. Moreover, the Wilkinson 2-way splitter 41 is configured to function equivalently as a high-pass filter, similar to the Wilkinson 2-way splitter 31 in the splitter 3 of the third embodiment. The distributed constant lines W3 and W4 at the cutoff frequency of the equivalently formed high-pass filter are regarded as a circuit pattern, and both ends of the series circuit of the inductor L5, resistor R3, and inductor L4 are at the same potential, and both ends of the series circuit of the capacitor C7, resistor R1, and capacitor C6 are also at the same potential, so no current flows, and these can be ignored. In addition, because the high-pass filter shares some of the elements that form the low-pass filter, in the Wilkinson 2-way distribution circuit 41 between the input terminal IN and the first output terminal OUT1, a π-type three-stage high-pass filter shown in FIG. 3(d) is equivalently formed by inductor L1 and the leakage inductance, capacitor C4, inductor L2 and the leakage inductance, and capacitor C1, and between the input terminal IN and the second output terminal OUT2, a π-type three-stage high-pass filter shown in FIG. 3(d) is equivalently formed by inductor L1 and the leakage inductance, capacitor C4, inductor L3 and the leakage inductance, and capacitor C5.

[0047] In this manner, in a state where a T-type three-stage low-pass filter is equivalently formed by the high-frequency transformer two-way distribution circuit 42, a π-type three-stage high-pass filter is equivalently formed by the Wilkinson two-way distribution circuit 41. As a result, as described above, the phase of the pass characteristic of the high-pass filter formed by the Wilkinson two-way distribution circuit 41 can be delayed relative to the phase of the pass characteristic of the low-pass filter formed by the high-frequency transformer two-way distribution circuit 42, and the phase of the pass characteristic can be matched when frequency bands are combined in a demultiplexing / mixing filter composed of the low-pass filter and the high-pass filter. The circuit constants are adjusted so that the cutoff frequency of the low-pass filter and the cutoff frequency of the high-pass filter coincide with each other.

[0048] 16 shows the frequency characteristics of the S parameters of the divider 4 having a division ratio of 2:1 according to the fourth embodiment of the present invention. The horizontal axis of FIG. 16 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 16, the pass characteristic |S21| between the input terminal IN and the second output terminal OUT2 to which 2 / 3 of the distributed signal power is output is a good frequency characteristic that maintains approximately -2 dB over the range of 10 MHz to 3224 MHz, and the pass characteristic |S31| between the input terminal IN and the first output terminal OUT1 to which 1 / 3 of the distributed signal power is output is a good frequency characteristic that maintains approximately -4.8 dB over the range of 10 MHz to 3224 MHz. In addition, the reflection characteristic |S11| of the input terminal IN is approximately -26 dB or less over the range of 10 MHz to 3224 MHz, the reflection characteristic |S22| of the second output terminal OUT2 is approximately -22 dB or less over the range of 10 MHz to 3224 MHz, and the reflection characteristic |S33| of the first output terminal OUT1 is approximately -19 dB or less over the range of 10 MHz to 3224 MHz, all of which are good frequency characteristics. Furthermore, the isolation characteristic |S32| between the first output terminal OUT1 and the second output terminal OUT2 is approximately -25 dB or more in the range of 10 MHz to 3224 MHz, which is considered to be a good frequency characteristic. In this way, the divider 4 with a division ratio of 2:1 in the fourth embodiment of the present invention is designed to operate in a frequency band of at least 10 MHz to 3224 MHz.

[0049] The equivalent circuit of the splitter 4 having a distribution ratio of 2:1 according to the fourth embodiment of the present invention is also the equivalent circuit shown in Fig. 4(a) described above. As described above, the equivalent circuit shown in Fig. 4(a) is composed of a demultiplexing / mixing filter 14 configured by connecting in parallel a low-pass filter formed by the high-frequency transformer 2-way distribution circuit 42 and a high-pass filter formed by the Wilkinson 2-way distribution circuit 41 between the input terminal IN and the first output terminal OUT1, and a demultiplexing / mixing filter 15 configured by connecting in parallel a low-pass filter formed by the high-frequency transformer 2-way distribution circuit 42 and a high-pass filter formed by the Wilkinson 2-way distribution circuit 41 between the input terminal IN and the second output terminal OUT2. In this case, the circuit constants of the Wilkinson 2-way distribution circuit 41 and the high-frequency transformer 2-way distribution circuit 42 are adjusted so that the cutoff frequencies of the low-pass filter and the high-pass filter coincide with each other. The cutoff frequency is set to, for example, 1 GHz.

[0050] In the branching / mixing filters 14 and 15, the usable frequency band of the Wilkinson 2-way distribution circuit 41 is approximately 1000 MHz to 3224 MHz, so the equivalent circuit of the branching / mixing filters 14 and 15 has the circuit configuration shown in Fig. 4(b) described above, and is a π-type three-stage high-pass filter. Also, the usable frequency band of the high-frequency transformer 2-way distribution circuit 42 is approximately 10 MHz to 1000 MHz, so the equivalent circuit of the branching / mixing filters 14 and 15 has the circuit configuration shown in Fig. 4(c) described above, and is a T-type three-stage low-pass filter. As a result, the phase of the pass characteristic of the high-pass filter formed by Wilkinson 2-way distribution circuit 41 lags behind the phase of the pass characteristic of the low-pass filter formed by high-frequency transformer 2-way distribution circuit 42 by 90 degrees, and the phases of the pass characteristics demultiplexed and mixed in the demultiplexing and mixing filters 14, 15 are matched. In this way, in the branching / mixing filters 14 and 15 of the distributor 4 according to the fourth embodiment of the present invention, the phases of the pass characteristics of the cutoff frequencies are matched and the frequency bands are combined without adding a phase correction circuit.

[0051] <Distributor according to the fifth embodiment of the present invention> FIG. 17 is a circuit diagram showing the configuration of a splitter 5 according to a fifth embodiment of the present invention. The splitter 5 according to the fifth embodiment of the present invention shown in FIG. 17 is a splitter 5 with a split number of 3. As shown in FIG. 17, the splitter 5 has an input terminal IN and three output terminals OUT51, OUT52, and OUT53, and each of the output terminals OUT51 to 53 outputs one-third of the split signal power. In other words, the splitter 5 according to the fifth embodiment is an equal splitter. The impedance of the input terminal IN and the output terminals OUT51, OUT52, and OUT53 is an impedance Zo. Zo is, for example, 75 Ω.

[0052] As shown in FIG. 17, the input terminal IN is connected to the input terminal of a distributor 3-1 with a division ratio of 2. The distributor 3-1 is any one of the distributor 1 of the first embodiment to the distributor 3 of the third embodiment of the present invention. The first output terminal of the distributor 3-1 is connected to the input terminal of the first distributor 4-1 with a division ratio of 2:1, and the second output terminal of the distributor 3-1 is connected to the input terminal of the second distributor 4-2 with a division ratio of 2:1. The first distributor 4-1 and the second distributor 4-2 are the distributor 4 of the fourth embodiment of the present invention. The output terminal of the first distributor 4-1 from which the divided 2 / 3 signal power is output is connected to the output terminal OUT51, and the output terminal of the first distributor 4-1 from which the divided 1 / 3 signal power is output is connected to the output terminal OUT52. In addition, the output terminal from which the distributed 1 / 3 of the signal power of the second distributor 4-2 is output is connected to the output terminal OUT52, and the output terminal from which the distributed 2 / 3 of the signal power of the first distributor 4-2 is output is connected to the output terminal OUT53. As a result, 1 / 2×2 / 3=1 / 3 of the signal power is output from output terminal OUT51, (1 / 2×1 / 3)+(1 / 2×1 / 3)=1 / 3 of the signal power is output from output terminal OUT52, and 1 / 2×2 / 3=1 / 3 of the signal power is output from output terminal OUT53. As described above, the divider 5 having a division ratio of 3 according to the fifth embodiment of the present invention is configured by combining any one of the divider 1 according to the first embodiment to the divider 3 according to the third embodiment of the present invention with the divider 4 according to the fourth embodiment of the present invention, and therefore the frequency band used is at least 10 MHz to 3224 MHz.

[0053] 18 shows the frequency characteristics of the S parameters of divider 5 with a division factor of 3 according to the fifth embodiment of the present invention. The horizontal axis of Fig. 18 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 18, the pass characteristic |S21| between the input terminal IN and the output terminal OUT51, the pass characteristic |S31| between the input terminal IN and the output terminal OUT52, and the pass characteristic |S41| between the input terminal IN and the output terminal OUT53 are almost the same frequency characteristic, and are good frequency characteristics that maintain about -4.8 dB from 10 MHz to 3224 MHz. The reflection characteristic |S11| of the input terminal IN is about -21 dB or less from 10 MHz to 3224 MHz, and is good frequency characteristics. The reflection characteristic |S22| of the output terminal OUT51 and the reflection characteristic |S44| of the output terminal OUT53 are almost the same frequency characteristic, and are about -21 dB or less from 10 MHz to 3224 MHz, and the reflection characteristic |S33| of the output terminal OUT52 is about -18 dB or less from 10 MHz to 3224 MHz, and are good frequency characteristics. Furthermore, the isolation characteristic |S32| between the output terminal OUT51 and the output terminal OUT52 is approximately -27 dB or more in the range of 10 MHz to 3224 MHz, which is considered to be a good frequency characteristic. Note that the isolation characteristic |S43| between the output terminal OUT52 and the output terminal OUT53 is similar to the isolation characteristic |S32|. In this way, the divider 5 with the division ratio of 3 in the fifth embodiment of the present invention operates in a frequency band of at least 10 MHz to 3224 MHz.

[0054] <Sixth embodiment of distributor according to the present invention> FIG. 19 is a circuit diagram showing the configuration of a splitter 6 according to a sixth embodiment of the present invention. The splitter 6 according to the sixth embodiment of the present invention shown in FIG. 19 is a splitter 6 with a split number of 4. As shown in FIG. 19, the splitter 6 has an input terminal IN and four output terminals OUT61, OUT62, OUT63, and OUT64, and each of the output terminals OUT61 to OUT64 outputs a quarter of the split signal power. That is, the splitter 6 according to the sixth embodiment is an equal splitter. The impedance of the input terminal IN and the output terminals OUT61, OUT62, OUT63, and OUT64 is an impedance Zo. Zo is, for example, 75 Ω.

[0055] As shown in FIG. 19, the input terminal IN is connected to the input terminal of the first distributor 3-1, which is an equal distributor with a distribution number of 2. The first output terminal of the first distributor 3-1 is connected to the input terminal of the second distributor 3-2, which is an equal distributor with a distribution number of 2, and the second output terminal of the first distributor 3-1 is connected to the input terminal of the third distributor 3-3, which is an equal distributor with a distribution number of 2. The first distributor 3-1 to the third distributor 3-3 are any of the distributor 1 of the first embodiment to the distributor 3 of the third embodiment of the present invention. The first output terminal of the second distributor 3-2 is connected to the output terminal OUT61, and the second output terminal of the second distributor 3-2 is connected to the output terminal OUT62. In addition, the first output terminal of the third distributor 3-3 is connected to the output terminal OUT63, and the second output terminal of the third distributor 3-3 is connected to the output terminal OUT64. As a result, 1 / 2×1 / 2=1 / 4 signal power is output from each of the output terminals OUT61 to OUT64. As described above, the distributor 6 with a division ratio of 4 in the sixth embodiment of the present invention is configured by combining three of any one of the distributors 1 in the first embodiment to the distributors 3 in the third embodiment of the present invention, and therefore the frequency band used is at least 10 MHz to 3224 MHz.

[0056] 20 shows the frequency characteristics of the S parameters of the divider 6 with a division factor of 4 according to the sixth embodiment of the present invention. The horizontal axis of FIG. 20 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 20, the transmission characteristic |S21| between the input terminal IN and the output terminal OUT61 is a good frequency characteristic that maintains approximately -6 dB over the range of 10 MHz to 3224 MHz. The reflection characteristic |S11| of the input terminal IN is approximately -23 dB or less over the range of 10 MHz to 3224 MHz, which is a good frequency characteristic. The reflection characteristic |S22| of the output terminal OUT61 is approximately -29 dB or less over the range of 10 MHz to 3224 MHz, which is a good frequency characteristic. Furthermore, the isolation characteristic |S32| between the output terminal OUT61 and the output terminal OUT62 is approximately -28 dB or more over the range of 10 MHz to 3224 MHz, which is a good frequency characteristic. The pass characteristic |S31| between the input terminal IN and the output terminal OUT62, the pass characteristic |S41| between the input terminal IN and the output terminal OUT63, and the pass characteristic |S51| between the input terminal IN and the output terminal OUT64 have frequency characteristics similar to the pass characteristic |S21|, and the reflection characteristic |S33| of the output terminal OUT62, the reflection characteristic |S44| of the output terminal OUT63, and the reflection characteristic |S55| of the output terminal OUT64 have frequency characteristics similar to the reflection characteristic |S22|. In this way, the divider 6 with a division ratio of 4 according to the sixth embodiment of the present invention operates in a frequency band of at least 10 MHz to 3224 MHz.

[0057] <Seventh embodiment of distributor according to the present invention> FIG. 21 is a circuit diagram showing the configuration of a splitter 7 according to a seventh embodiment of the present invention. The splitter 7 according to the seventh embodiment of the present invention shown in FIG. 21 is a splitter 7 with a split number of 6. As shown in FIG. 21, the splitter 7 has an input terminal IN and six output terminals OUT71, OUT72, OUT73, OUT74, OUT75, and OUT76, and each of the output terminals OUT71 to 76 outputs 1 / 6 of the split signal power. That is, the splitter 7 according to the seventh embodiment is an equal splitter. The impedance of the input terminal IN and the output terminals OUT71, OUT72, OUT73, OUT74, OUT75, and OUT76 is an impedance Zo. Zo is, for example, 75Ω.

[0058] As shown in FIG. 21, the input terminal IN is connected to the input terminal of the first distributor 3-1, which is an equal distributor with a distribution number of 2. The first distributor 3-1 is any one of the distributor 1 of the first embodiment to the distributor 3 of the third embodiment of the present invention. The first output terminal of the first distributor 3-1 is connected to the input terminal of the second distributor 5-1, which is an equal distributor with a distribution number of 3, and the second output terminal of the first distributor 3-1 is connected to the input terminal of the third distributor 5-2, which is an equal distributor with a distribution number of 3. The second distributor 5-1 and the third distributor 5-2 are the distributor 5 with a distribution number of 3 of the fifth embodiment of the present invention. The first output terminal of the second distributor 5-1 is connected to the output terminal OUT71, the second output terminal of the second distributor 5-1 is connected to the output terminal OUT72, and the third output terminal of the second distributor 5-1 is connected to the output terminal OUT73. In addition, the first output terminal of the third distributor 5-2 is connected to the output terminal OUT74, the second output terminal of the third distributor 5-2 is connected to the output terminal OUT75, and the third output terminal of the third distributor 5-2 is connected to the output terminal OUT76. As a result, 1 / 2×1 / 3=1 / 6 signal power is output from each of the output terminals OUT71 to 76. As described above, the divider 7 of the seventh embodiment of the present invention with a division ratio of 6 is configured by combining any one of the divider 1 of the first embodiment to the divider 3 of the third embodiment of the present invention and the divider 5 of the fifth embodiment of the present invention which is a combination of any one of the divider 1 of the first embodiment to the divider 3 of the third embodiment of the present invention and the divider 4 of the fourth embodiment, and therefore the frequency band used is at least 10 MHz to 3224 MHz.

[0059] 22 shows the frequency characteristics of the S parameters of the divider 7 according to the seventh embodiment of the present invention, with the number of divisions being 6. The horizontal axis of FIG. 22 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 22, the transmission characteristic |S21| between the input terminal IN and the output terminal OUT71 is a good frequency characteristic that maintains approximately -8 dB from 10 MHz to 3224 MHz. Also, the reflection characteristic |S11| of the input terminal IN is approximately -20 dB or less from 10 MHz to 3224 MHz, which is a good frequency characteristic. Furthermore, the reflection characteristic |S22| of the output terminal OUT71 is approximately -21 dB or less from 10 MHz to 3224 MHz, which is a good frequency characteristic. Furthermore, the isolation characteristic |S32| between the output terminal OUT71 and the output terminal OUT72 is approximately -28 dB or more from 10 MHz to 3224 MHz, which is a good frequency characteristic. The pass characteristic |S31| between the input terminal IN and the output terminal OUT72, the pass characteristic |S41| between the input terminal IN and the output terminal OUT73, the pass characteristic |S51| between the input terminal IN and the output terminal OUT74, the pass characteristic |S61| between the input terminal IN and the output terminal OUT75, and the pass characteristic |S71| between the input terminal IN and the output terminal OUT76 have frequency characteristics similar to the pass characteristic |S21|, and the reflection characteristic |S33| of the output terminal OUT72, the reflection characteristic |S44| of the output terminal OUT73, the reflection characteristic |S55| of the output terminal OUT74, the reflection characteristic |S66| of the output terminal OUT75, and the reflection characteristic |S77| of the output terminal OUT76 have frequency characteristics similar to the reflection characteristic |S22|. In this way, the divider 7 with a division ratio of 6 in the seventh embodiment of the present invention operates in a frequency band of at least 10 MHz to 3224 MHz.

[0060] <Distributor according to the eighth embodiment of the present invention> FIG. 23 is a circuit diagram showing the configuration of a splitter 8 according to an eighth embodiment of the present invention. The splitter 8 according to the eighth embodiment of the present invention shown in FIG. 23 is a splitter 8 with a split number of 8. As shown in FIG. 23, the splitter 8 has an input terminal IN and eight output terminals OUT81, OUT82, OUT83, OUT84, OUT85, OUT86, OUT87, and OUT88, and each of the output terminals OUT81 to 88 outputs 1 / 8 of the split signal power. That is, the splitter 8 according to the eighth embodiment is an equal splitter. The impedance of the input terminal IN and the output terminals OUT81, OUT82, OUT83, OUT84, OUT85, OUT86, OUT87, and OUT8 is an impedance Zo. Zo is, for example, 75Ω.

[0061] As shown in FIG. 23, the input terminal IN is connected to the input terminal of the first distributor 3-1, which is an equal distributor with a distribution number of 2. The first distributor 3-1 is any one of the distributor 1 of the first embodiment to the distributor 3 of the third embodiment of the present invention. The first output terminal of the first distributor 3-1 is connected to the input terminal of the second distributor 6-1, which is an equal distributor with a distribution number of 4, and the second output terminal of the first distributor 3-1 is connected to the input terminal of the third distributor 6-2, which is an equal distributor with a distribution number of 4. The second distributor 6-1 and the third distributor 6-2 are the distributor 6 with a distribution number of 4 of the sixth embodiment of the present invention. The first output terminal of the second distributor 6-1 is connected to the output terminal OUT81, the second output terminal of the second distributor 6-1 is connected to the output terminal OUT82, the third output terminal of the second distributor 6-1 is connected to the output terminal OUT83, and the fourth output terminal of the second distributor 6-1 is connected to the output terminal OUT84. In addition, the first output terminal of the third distributor 6-2 is connected to the output terminal OUT85, the second output terminal of the third distributor 6-2 is connected to the output terminal OUT86, the third output terminal of the third distributor 6-2 is connected to the output terminal OUT87, and the fourth output terminal of the third distributor 6-2 is connected to the output terminal OUT88. As a result, 1 / 2×1 / 4=1 / 8 signal power is output from each of the output terminals OUT81 to OUT88. As described above, the divider 8 of the eighth embodiment of the present invention having a division ratio of 8 is configured by combining any one of the divider 1 of the first embodiment to the divider 3 of the third embodiment of the present invention with the divider 6 of the sixth embodiment of the present invention which is a combination of three of the dividers 1 of the first embodiment to the third embodiment of the present invention, and therefore the frequency band used is at least 10 MHz to 3224 MHz.

[0062] Fig. 24 shows the frequency characteristics of the S parameters of divider 8 having a division factor of 8 according to the eighth embodiment of the present invention. The horizontal axis of Fig. 24 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 24, the transmission characteristic |S21| between the input terminal IN and the output terminal OUT81 is a good frequency characteristic that maintains approximately -9 dB over the range of 10 MHz to 3224 MHz. The reflection characteristic |S11| of the input terminal IN is approximately -22 dB or less over the range of 10 MHz to 3224 MHz, which is a good frequency characteristic. The reflection characteristic |S22| of the output terminal OUT81 is approximately -30 dB or less over the range of 10 MHz to 3224 MHz, which is a good frequency characteristic. Furthermore, the isolation characteristic |S32| between the output terminal OUT81 and the output terminal OUT82 is approximately -27 dB or more over the range of 10 MHz to 3224 MHz, which is a good frequency characteristic. In addition, the pass characteristic |S31| between the input terminal IN and the output terminal OUT82, the pass characteristic |S41| between the input terminal IN and the output terminal OUT83, the pass characteristic |S51| between the input terminal IN and the output terminal OUT84, the pass characteristic |S61| between the input terminal IN and the output terminal OUT85, the pass characteristic |S71| between the input terminal IN and the output terminal OUT86, the pass characteristic |S81| between the input terminal IN and the output terminal OUT87, and the pass characteristic |S The reflection characteristic |S91| has the same frequency characteristics as the pass characteristic |S21|, and the reflection characteristic |S33| of output terminal OUT82, the reflection characteristic |S44| of output terminal OUT83, the reflection characteristic |S55| of output terminal OUT84, the reflection characteristic |S66| of output terminal OUT85, the reflection characteristic |S77| of output terminal OUT86, the reflection characteristic |S88| of output terminal OUT87, and the reflection characteristic |S99| of output terminal OUT88 have the same frequency characteristics as the reflection characteristic |S22|. In this way, the divider 8 with a division ratio of 8 according to the eighth embodiment of the present invention operates in a frequency band of at least 10 MHz to 3224 MHz.

[0063] FIG. 25 shows a circuit diagram illustrating the configuration of a splitter 9 according to a ninth embodiment of the present invention. The splitter 9 according to the ninth embodiment of the present invention shown in FIG. 25 is a splitter 9 with one branch. As shown in FIG. 25, the splitter 9 includes an input terminal IN, an output terminal OUT91, and a branch terminal OUT92, and the branched signal power is output from the branch terminal OUT92. The impedance of the input terminal IN, the output terminal OUT91, and the branch terminal OUT92 is impedance Zo. Zo is set to, for example, 75Ω. A directional coupling line branch circuit 91 and a branch transformer branch circuit 92 are connected in parallel between the input terminal IN, the output terminal OUT91, and the branch terminal 92. The frequency band used by the splitter 9 according to the ninth embodiment of the present invention is at least 10 MHz to 3224 MHz.

[0064] The directional coupling line branch circuit 91 has a directional coupling line 91a consisting of a distributed parameter line W11 and a distributed parameter line W12 arranged adjacent to the distributed parameter line W11, with a capacitor C11 connected between an input terminal IN and one end of the distributed parameter line W11, and a capacitor C12 connected between the other end of the distributed parameter line W11 and an output terminal OUT91. The other end of the capacitor C13 is connected to one end of the distributed parameter line W12, one end of the capacitor C13 is connected to a branch terminal OUT92 via an attenuator 93, and the other end of the distributed parameter line W12 is grounded via a resistor R11. The branch transformer branch circuit 92 has a branch transformer 92a consisting of a transformer T11 and a transformer T12. An inductor L11 is connected between an input terminal IN and one end of the primary side of the transformer T11, and an inductor L12 is connected between the other end of the primary side and an output terminal OUT91. One end of the secondary side of the transformer T11 is grounded, and the other end of the secondary side is connected to the other end of the secondary side of the transformer T12. One end of the primary side of the transformer T12 is grounded, and the other end of the primary side is connected to the other end of the primary side of the transformer T11. One end of the secondary side of the transformer T12 is connected to the other end of the inductor L13, and one end of the inductor L13 is connected to the branch terminal 92 via an attenuator 93. A capacitor C14 is connected between the connection point between the inductor L11 and one end of the primary side of the transformer T11 and the ground. The other end of the secondary side of the transformer T12 is grounded via a resistor R12. The attenuator 93 is a π-type attenuator including a resistor R13 connected in series to the branch terminal OUT92, and resistors R14 and R15 connected between both ends of the resistor R13 and the ground, respectively, and adjusts the amount of branching.

[0065] The branch transformer branch circuit 92 between the input terminal IN and the output terminal OUT91 functions as an equivalent T-type three-stage low-pass filter by the inductor L11, the capacitor C14, and the leakage inductance of the branch transformer 92a. Specifically, the inductor L12 is connected for correcting the leakage inductance value, and the inductor L11, the capacitor C14, and the inductor consisting of the leakage inductance and the inductor L12 form an equivalent T-type three-stage low-pass filter. In addition, the branch transformer branch circuit 92 between the input terminal IN and the branch terminal OUT92 forms an equivalent T-type three-stage low-pass filter by the inductor L11, the capacitor C14, and the inductor L13. This allows the branch transformer branch circuit 92 to function as a low-pass filter when synthesizing frequency bands.

[0066] The directional coupling line branch circuit 91 between the input terminal IN and the output terminal OUT91 functions as an equivalent π-type three-stage high-pass filter by the inductor L11, the other end of which is equivalently grounded, the capacitors C11 and C12, and the inductor L12, one end of which is equivalently grounded. Specifically, the inductor L11, the capacitors C11 and C12, the leakage inductance, and the inductor L12 form an equivalent π-type three-stage high-pass filter. The directional coupling line branch circuit 91 between the input terminal IN and the branch terminal OUT92 forms an equivalent π-type three-stage high-pass filter by the inductor L11, the other end of which is equivalently grounded, the capacitors C11 and C13, and the inductor L13, one end of which is equivalently grounded. This allows the directional coupling line branch circuit 91 to function as a high-pass filter when frequency bands are combined. The capacitor C13 and the inductor L13 are elements for finely adjusting the cutoff frequency on the branch terminal OUT92 side.

[0067] In this manner, in a state where a T-type three-stage low-pass filter is equivalently formed by the branch transformer branch circuit 92, a π-type three-stage high-pass filter is equivalently formed by the directional coupling line branch circuit 91. As a result, as described above, the phase of the pass characteristic of the high-pass filter formed by the directional coupling line branch circuit 91 can be delayed relative to the phase of the pass characteristic of the low-pass filter formed by the branch transformer branch circuit 92, and the phases of the pass characteristics can be matched when frequency bands are synthesized in a branching / mixing filter composed of the low-pass filter and the high-pass filter. The circuit constants are adjusted so that the cutoff frequency of the low-pass filter and the cutoff frequency of the high-pass filter coincide with each other. In this way, in the distributor 9 of the ninth embodiment of the present invention, the phase of the pass characteristic of the cutoff frequency is matched and the frequency bands are combined without adding a phase correction circuit.

[0068] Fig. 26 shows the frequency characteristics of the S-parameters of the splitter 9 of the ninth embodiment of the present invention. The horizontal axis of Fig. 26 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. The cutoff frequency of the high-pass filter equivalently formed by the directional coupling line splitter circuit 91 and the low-pass filter equivalently formed by the splitter transformer splitter circuit 92 are the same, and is set to 1 GHz here. 26, the pass characteristic |S21| between the input terminal IN and the output terminal OUT91 is a good frequency characteristic that is maintained between about 0 and -0.5 dB over the range of 10 MHz to 3224 MHz. Also, the pass characteristic |S31| between the input terminal IN and the branch terminal 92 is a good frequency characteristic that is maintained at about -20 dB over the range of 10 MHz to 3224 MHz. Also, the reflection characteristic |S11| of the input terminal IN is about -32 dB or less over the range of 10 MHz to 3224 MHz, the reflection characteristic |S22| of the output terminal OUT91 is about -30 dB or less over the range of 10 MHz to 3224 MHz, and the reflection characteristic |S33| of the branch terminal OUT92 is about -29 dB or less over the range of 10 MHz to 3224 MHz, which are good frequency characteristics. Furthermore, the isolation characteristic |S32| between the output terminal OUT91 and the branch terminal OUT92 is approximately -30 dB or more in the range of 10 MHz to 3224 MHz, which is considered to be a good frequency characteristic. In this way, the splitter 9 according to the ninth embodiment of the present invention is designed to operate in a frequency band of at least 10 MHz to 3224 MHz.

[0069] <Distributor according to the tenth embodiment of the present invention> A circuit diagram showing the configuration of a splitter 200 according to a tenth embodiment of the present invention is shown in Fig. 27. The splitter 200 according to the tenth embodiment of the present invention shown in Fig. 27 is a wideband splitter 200 with a split ratio of 1:1 and a split number of 2, which is composed of a Wilkinson 2-way splitter circuit 201 and a high-frequency transformer 2-way splitter circuit 202. In this way, the splitter 200 according to the tenth embodiment is an equal splitter. As shown in FIG. 27, a distributor 200 with a distribution number of 2 includes an input terminal IN and two output terminals OUT1 and OUT2, and the output terminals OUT1 and OUT2 are distribution terminals. The input terminal IN and the output terminals OUT1 and OUT2 all have the same impedance Zo, for example, 75Ω. Between the input terminal IN and the output terminals OUT1 and OUT2, a Wilkinson 2-way distribution circuit 201 and a high-frequency transformer 2-way distribution circuit 202 are connected in parallel. In the distributor 200 of the tenth embodiment of the present invention, the frequency bands of 770MHz to 1030MHz or 962MHz to 1030MHz in the band of 10MHz to 3224MHz are unused bands, and the usable frequency band of the tenth embodiment of the present invention is divided into a low band from 10MHz to a predetermined lower limit frequency of the unused band, and a high band from a predetermined upper limit frequency of the unused band to 3224MHz.

[0070] The Wilkinson 2-way distribution circuit 201 is configured such that capacitors C8 and C9 are inserted between the capacitors C1 and C5 and the distributed constant lines W1 and W2 in the Wilkinson 2-way distribution circuit 31 of the distributor 3 of the third embodiment. In addition, inductors L6 and L7 are connected between the connection point of the capacitors C1 and C9 and the ground, and between the connection point of the capacitors C5 and C8 and the ground, respectively, and a resistor R4 is connected between both connection points. That is, in the Wilkinson 2-way distribution circuit 201, a series circuit of a capacitor C1 having one end connected to the input terminal IN, a capacitor C9 having one end connected to the other end of the capacitor C1, and a distributed constant line W1 having the other end connected to the first output terminal OUT1 is connected between the input terminal IN and the first output terminal OUT1. In addition, a series circuit of a capacitor C5 having one end connected to the input terminal IN, a capacitor C8 having one end connected to the other end of the capacitor C5, and a distributed constant line W2 having the other end connected to the second output terminal OUT2 is connected between the input terminal IN and the second output terminal OUT2. Furthermore, a resistor R4 is connected between the connection point of the capacitors C1 and C9 and the connection point of the capacitors C5 and C8, and a series circuit of a resistor R3 and an inductor L4 is connected between the connection point of the other end of the capacitor C9 and one end of the distributed parameter line W1 and the connection point of the other end of the capacitor C8 and one end of the distributed parameter line W2. Furthermore, an inductor L7 is connected between the connection point of the capacitors C1 and C9 and the ground, and an inductor L6 is connected between the connection point of the capacitors C5 and C8 and the ground. Furthermore, a series circuit of a resistor R1 and a capacitor C6 is connected between the other end of the distributed parameter line W1 and the other end of the distributed parameter line W2. The resistor R1 is used for isolation between the output terminals OUT1 and OUT2. In this way, in the Wilkinson 2-way distribution circuit 201, signals that are equally distributed with a distribution ratio of 1:1 are output from the other ends of the distributed constant lines W1 and W2, and one of the equally distributed distribution signals is output from the first output terminal OUT1, and the other equally distributed distribution signal is output from the second output terminal OUT2. Also, the high frequency transformer 2 distribution circuit 202 is configured by omitting the resistor R2 in the high frequency transformer 2 distribution circuit 12 in the distributor 1 of the first embodiment, but performs the same function as the high frequency transformer 2 distribution circuit 12. That is, in the high frequency transformer 2 distribution circuit 202, signals equally distributed at a distribution ratio of 1:1 are output from both ends of the secondary coil S of the distribution transformer T1, one of the equally distributed distribution signals is output from the first output terminal OUT1, and the other equally distributed distribution signal is output from the second output terminal OUT2.

[0071] In the distributor 200 according to the tenth embodiment of the present invention, the high frequency transformer 2 distribution circuit 202 functions as an equivalent T-type three-stage low-pass filter due to the leakage inductance generated in the distribution transformer T1 and the capacitor C4. This allows the high frequency transformer 2 distribution circuit 202 to function as a low-pass filter when combining frequency bands. Inductors L1, L2, and L3 are connected for compensating for the leakage inductance value. Also, the Wilkinson 2-way distribution circuit 201 functions as a 3-stage 2-way distribution circuit including an initial stage 2-way distribution circuit combining capacitors C1, C5 and a composite inductance of the inductor L1 in the high frequency transformer 2-way distribution circuit 202 and the leakage inductance generated in the primary coil P of the distribution transformer T1, a middle stage 2-way distribution circuit combining capacitors C8, C9 and inductors L6, L7, and a final stage 2-way distribution circuit combining distributed constant lines W1, W2 and a composite inductance of the inductors L2, L3 in the high frequency transformer 2-way distribution circuit 202 and the leakage inductance generated in the secondary coil S of the distribution transformer T1. Resistor R4 is for isolation of the initial stage 2-way distribution circuit, resistor R3 and inductor L4 are for isolation of the middle stage 2-way distribution circuit, and resistor R1 and capacitor C6 are isolation elements of the final stage 2-way distribution circuit.

[0072] Furthermore, the Wilkinson 2-way distributor 201 is configured to function equivalently as a high-pass filter. The distributed constant lines W1 and W2 at the cutoff frequency of the equivalently formed high-pass filter are regarded as a circuit pattern, and both ends of the resistor R4 and both ends of the series circuit of the resistor R3 and inductor L4 are at the same potential, and both ends of the series circuit of the resistor R1 and capacitor C6 are also at the same potential, so that no current flows, and therefore the resistor R4, resistor R3, inductor L4, resistor R1, and capacitor C6 can be ignored. In addition, because the high-pass filter shares some of the elements that form the low-pass filter, in Wilkinson 2-way distribution circuit 201 between input terminal IN and first output terminal OUT1, a π-type five-stage high-pass filter is equivalently formed by inductor L1 and the leakage inductance, capacitor C4, inductor L2 and the leakage inductance, capacitor C1, inductor L7, and capacitor C9, and between input terminal IN and second output terminal OUT2, a π-type five-stage high-pass filter is equivalently formed by inductor L1 and the leakage inductance, capacitor C4, inductor L3 and the leakage inductance, capacitor C5, inductor L6, and capacitor C8.

[0073] In this way, the high frequency transformer 2-way distribution circuit 202 forms an equivalent three-stage T-type low-pass filter, while the Wilkinson 2-way distribution circuit 201 forms an equivalent five-stage π-type high-pass filter. In this case, since the number of elements in the high-pass filter is five, the phase change is 5×90 degrees=450 degrees=+90 degrees. Therefore, the phase of the pass characteristic of the high-pass filter formed by the Wilkinson 2-way distribution circuit 201 advances with respect to the phase of the pass characteristic of the low-pass filter formed by the high frequency transformer 2-way distribution circuit 202, and in the demultiplexing / mixing filter composed of the low-pass filter and the high-pass filter, the phases of the pass characteristics are mismatched when the frequency bands are synthesized. In this case, the circuit constants are adjusted so that the cutoff frequency of the low-pass filter and the cutoff frequency of the high-pass filter are a desired frequency in the unused band, for example, 920 MHz. Since the phase of the pass characteristic is mismatched, a steep attenuation waveform is generated at the cutoff frequency, but at other frequencies, the distributor 200 of the tenth embodiment of the present invention is realized, which has good distribution performance over a wide band. In this way, in the distributor 200 of the tenth embodiment of the present invention, the circuit configuration and number of stages of the low-pass filter and the high-pass filter are configured so as to match the cutoff frequencies of the low-pass filter and the high-pass filter, without being restricted by the condition for matching the phase of the pass characteristics.

[0074] The transmission characteristics of the S parameters of the splitter 200 according to the tenth embodiment of the present invention are shown in Fig. 28. The horizontal axis of Fig. 28 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 28, the pass characteristic |S21| between the input terminal IN and the first output terminal OUT1 has good frequency characteristics that maintain approximately -3 dB except for the frequency band around 920 MHz among 10 MHz to 3224 MHz. It can be seen that the pass characteristic |S21| has a notch shape with a steep attenuation waveform at the cutoff frequency of 920 MHz. Although not shown, the pass characteristic |S31| between the input terminal IN and the second output terminal OUT2 also has a notch shape with a steep attenuation waveform at the cutoff frequency of 920 MHz.

[0075] Next, the frequency characteristics of the S parameters of the splitter 200 according to the tenth embodiment of the present invention are shown in Fig. 29. The horizontal axis of Fig. 29 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 29, the pass characteristic |S21| between the input terminal IN and the first output terminal OUT1 and the pass characteristic |S31| between the input terminal IN and the second output terminal OUT2 are almost the same frequency characteristic, and are good frequency characteristics that maintain about -3 dB in the low frequency range of 10 MHz to less than 920 MHz and in the high frequency range of more than 920 MHz to 3224 MHz. In addition, the reflection characteristic |S11| of the input terminal IN is about -20 dB or less in the range of 10 MHz to 3224 MHz except for the band near 920 MHz, and the reflection characteristic |S22| of the first output terminal OUT1 and the reflection characteristic |S33| of the second output terminal OUT2 are almost the same frequency characteristic as the reflection characteristic |S11|, and are good frequency characteristics. Furthermore, the isolation characteristic |S32| between the first output terminal OUT1 and the second output terminal OUT2 is about -22 dB or more except for the band near 920 MHz, and are good frequency characteristics.

[0076] In this way, since 770 MHz to 1030 MHz is considered to be an unused band in the 10 MHz to 3224 MHz band, the operating frequency band of the distributor 200 of the tenth embodiment of the present invention is a frequency band in which the low frequency range from 10 MHz to a predetermined lower limit frequency of the unused band, and the high frequency range from a predetermined upper limit frequency of the unused band to 3224 MHz, are operating well. The splitter 200 of the tenth embodiment of the present invention is configured with a demultiplexing / mixing filter configured by connecting in parallel between the input terminal IN and the first output terminal OUT1 a low-pass filter formed by the high-frequency transformer 2-way distribution circuit 202 and a high-pass filter formed by the Wilkinson 2-way distribution circuit 201, and a demultiplexing / mixing filter configured by connecting in parallel between the input terminal IN and the second output terminal OUT2 a low-pass filter formed by the high-frequency transformer 2-way distribution circuit 202 and a high-pass filter formed by the Wilkinson 2-way distribution circuit 201. The cutoff frequencies of the low-pass filter formed by the high-frequency transformer 2-way distribution circuit 202 and the high-pass filter formed by the Wilkinson 2-way distribution circuit 201 are the same, and the frequency bands are synthesized in the low range from 10 MHz to approximately the cutoff frequency and in the high range from approximately the cutoff frequency to 3224 MHz. Note that the phase of the pass characteristic is in a mismatched state in the band of 10 MHz to 3224 MHz. In this case, the cutoff frequency can be a predetermined frequency in an unused frequency band. For example, if the cutoff frequency is set to 920 MHz, the frequency characteristics of the S parameters will be good in the low frequency band from 10 MHz to less than 920 MHz, and in the high frequency band from frequencies above 920 MHz to 3224 MHz.

[0077] <Distributor according to the 11th embodiment of the present invention> It has been confirmed that in the distributor 3 of the third embodiment of the present invention, which has the circuit diagram shown in Fig. 13, depending on the distribution transformer T1 used, the frequency characteristics of the S parameters may become those shown in Fig. 30. The horizontal axis of Fig. 30 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 30, the pass characteristic |S21| between the input terminal IN and the first output terminal OUT1 and the pass characteristic |S31| between the input terminal IN and the second output terminal OUT2 are almost the same frequency characteristic, and are good frequency characteristics that maintain about -3 dB from 10 MHz to 3224 MHz. In addition, the reflection characteristic |S11| of the input terminal IN is about -28 dB or less from 10 MHz to 3224 MHz, and is good frequency characteristics. However, the reflection characteristic |S22| of the first output terminal OUT1 and the reflection characteristic |S33| of the second output terminal OUT2 are almost the same frequency characteristic, and are degraded to about -16 dB or less from 10 MHz to 3224 MHz. Furthermore, the isolation characteristic |S32| between the first output terminal OUT1 and the second output terminal OUT2 is also degraded to about -16 dB or less from 10 MHz to 3224 MHz.

[0078] The causes of deterioration of the reflection characteristic |S22| of the first output terminal OUT1, the reflection characteristic |S33| of the second output terminal OUT2, and the isolation characteristic |S32| between the first output terminal OUT1 and the second output terminal OUT2 will be considered. The distribution transformer T1 is composed of a primary coil P and a secondary coil S, and if the winding manner of these coils is different, the electrical characteristics of the distribution transformer T1 may differ. Therefore, the distribution transformer T1 used when showing the frequency characteristics of the S parameters shown in FIG. 30 was analyzed. As described above, the circuit of the distribution transformer T1 is the circuit shown in FIG. 31(a), and the analysis revealed that the primary coil P having the impedance conversion function of the distribution transformer T1 exhibits a good impedance conversion function in the frequency band up to 3224 MHz. In addition, it was found that in the secondary coil S of the distribution transformer T1, a resistance component RL that functions in a low frequency range of about 1 GHz or less and a resistance component RH that functions in a high frequency range of about 1 GHz or more are equivalently generated between the distribution output terminals as shown in FIG. 31(b). In FIG. 31(b), in order to show that the resistance components are equivalently generated in the low frequency range and the high frequency range, an inductor LL is connected in series to the resistance component RL that functions in the low frequency range, and a capacitor CH is connected in series to the resistance component RH that functions in the high frequency range. In the frequency characteristics of the S parameters shown in Fig. 30, the reflection characteristic |S11|, reflection characteristic |S22|, and reflection characteristic |S33| show deterioration in the frequency characteristics on the low frequency side, which suggests that the above-mentioned frequency characteristics are deteriorated mainly by the resistance component RL that functions in the low frequency range. In other words, the resistance component RL that functions in the low frequency range is connected in parallel to the isolation resistor R3, and interferes with the resistor R3. As a result, it is believed that the resistor R3 cannot obtain optimal matching.

[0079] Therefore, a circuit diagram showing the configuration of a divider 300 according to an eleventh embodiment of the present invention that is designed to avoid the influence of the resistance component RL that functions in the low range is shown in Fig. 32. The divider 300 according to the eleventh embodiment of the present invention shown in Fig. 32 is a wideband divider 300 with a division ratio of 1:1 and a division number of 2, which is composed of a Wilkinson 2-way divider circuit 301 and a high-frequency transformer 2-way divider circuit 302. In this way, the divider 300 according to the eleventh embodiment is an equal divider. As shown in Fig. 32, a distributor 300 with a division ratio of 2 includes an input terminal IN and two output terminals OUT1 and OUT2, and the output terminals OUT1 and OUT2 are used as distribution terminals. The input terminal IN and the output terminals OUT1 and OUT2 all have the same impedance Zo, for example, 75Ω. A Wilkinson 2-way distribution circuit 301 and a high-frequency transformer 2-way distribution circuit 302 are connected in parallel between the input terminal IN and the output terminals OUT1 and OUT2. The frequency band used by the distributor 3 in the eleventh embodiment of the present invention is at least 10 MHz to 3224 MHz.

[0080] In the divider 300 of the eleventh embodiment of the present invention, a capacitor C10 is inserted between the other end of the distributed constant line W1 and the first output terminal OUT1, and a capacitor C11 is inserted between the other end of the distributed constant line W2 and the second output terminal OUT2 in the divider 3 of the third embodiment shown in FIG. 13. The other configurations are the same as those of the divider 3 of the third embodiment. Since the capacitors C10 and C11 show a large impedance in the low frequency band, they are less susceptible to the influence of the resistance component RL that functions in the low frequency band, and the resistance value of the isolation resistor R3 maintains a predetermined value in the low frequency band, thereby obtaining optimal matching. Here, the resistance component RH is a resistance component that functions in the high frequency band, and since the impedances of the inductors L2 and L3 show a large impedance, there is no interference with other resistors in the Wilkinson 2-way divider circuit 301. It was confirmed that the frequency characteristics of the S parameters were improved by inserting and connecting the capacitors C10 and C11 as described above. With the exception of capacitors C10 and C11, the function is the same as that of the distributor 3 of the third embodiment described above, and therefore a description thereof will be omitted. However, the matching resistor R3 in the first stage of the Wilkinson 2-way distribution circuit 301 is configured to share the matching resistor of the high-frequency transformer 2-way distribution circuit 302.

[0081] The frequency characteristics of the S parameters of the distributor 300 according to the eleventh embodiment of the present invention are shown in Fig. 33. The horizontal axis of Fig. 33 is frequency [GHz], and the vertical axis is absolute value (magnitude) [dB]. 33, the pass characteristic |S21| between the input terminal IN and the first output terminal OUT1 and the pass characteristic |S31| between the input terminal IN and the second output terminal OUT2 are almost the same frequency characteristic, and are good frequency characteristics that maintain about -3 dB from 10 MHz to 3224 MHz. The reflection characteristic |S11| of the input terminal IN is about -27 dB or less from 10 MHz to 3224 MHz, and the reflection characteristic |S22| of the first output terminal OUT1 and the reflection characteristic |S33| of the second output terminal OUT2 are almost the same frequency characteristic, and are about -29 dB or less from 10 MHz to 3224 MHz, and are good frequency characteristics. Furthermore, the isolation characteristic |S32| between the first output terminal OUT1 and the second output terminal OUT2 is about -27 dB or more from 10 MHz to 3224 MHz, and are good frequency characteristics. In this way, even if a resistance component RL that functions in a low frequency range and a resistance component RH that functions in a high frequency range are equivalently generated between the distribution output terminals in the secondary coil S of the distribution transformer T1, the frequency characteristics of the S parameters can be improved in the distributor 300 of the eleventh embodiment of the present invention. [Industrial Applicability]

[0082] The splitter according to the embodiment of the present invention described above is configured to delay the phase of the pass characteristic of the high-pass filter formed by the Wilkinson two-way splitter with respect to the phase of the pass characteristic of the low-pass filter formed by the high-frequency transformer two-way splitter, and thus the phases of the pass characteristics of the low-pass filter and the high-pass filter are matched to synthesize the frequency bands. At this time, the Wilkinson two-way splitter may be multi-staged to achieve a wider band. When the Wilkinson 2-way splitter circuit is configured in multiple stages, if the low-pass filter formed by the high-frequency transformer 2-way splitter circuit functions equivalently as a 4n-1 (n = 1, 2, 3, . . .)-stage T-type low-pass filter, then if the Wilkinson 2-way splitter circuit is configured so that the high-pass filter functions equivalently as a three-stage π-type high-pass filter, the phases of the pass characteristics of the low-pass filter and high-pass filter will be matched and the frequency bands will be combined. In addition, when the low-pass filter functions equivalently as a 4n+1 (n=1, 2, 3, . . .) stage T-type low-pass filter, if the Wilkinson 2-way distributor circuit is configured so that the high-pass filter functions equivalently as a 4n+3 (n=1, 2, 3, . . .) stage π-type high-pass filter, the phases of the pass characteristics of the low-pass filter and the high-pass filter will be matched and the frequency bands will be combined. Furthermore, when the low-pass filter functions equivalently as a 4n+3 (n=1, 2, 3, . . .) stage T-type low-pass filter, if the Wilkinson 2-way distributor is configured so that the high-pass filter functions equivalently as a 4n+1 (n=1, 2, 3, . . .) stage π-type high-pass filter, the phases of the pass characteristics of the low-pass filter and the high-pass filter will be matched and the frequency bands will be combined. In the distributor of the embodiment of the present invention described above, an equivalent branching / mixing filter is formed, and in the branching / mixing filter, the phase of the pass characteristic of the cutoff frequency is matched without adding a phase correction circuit, and the frequency bands are combined. In the splitter and branching device according to the embodiment of the present invention described above, a demultiplexing / mixing filter is formed by a low-pass filter formed by a high-frequency transformer 2-way splitting circuit and a high-pass filter formed by a Wilkinson 2-way splitting circuit, and in the demultiplexing / mixing filter, the phase of the pass characteristic of the cutoff frequency is matched without adding a phase correction circuit, and the frequency band is synthesized. In addition, the usable frequency band can be made wide, from 10 MHz to 3224 MHz. Furthermore, in the splitter and branching device according to the embodiment of the present invention, the distributed constant line can be configured with a microstrip line.

[0083] The frequency band used by the distributor and splitter in the embodiment of the present invention described above is 10MHz to 3224MHz. That is, the frequency band used by the distributor and splitter in the embodiment of the present invention can be applied to an intra-building shared viewing system. In this case, the transmission frequency band of the intra-building shared viewing system is 10MHz to 60MHz or 10MHz to 55MHz for the CATV upstream signal, 70MHz to 770MHz or 70MHz to 962MHz for the CATV downstream signal, and 1032MHz to 3224MHz for the BS / CS-IF received signal. Then, in the usable frequency band of 10 MHz to 3224 MHz of the distributor according to the tenth embodiment of the present invention, 770 MHz (962 MHz) to 1030 MHz is an unused band, and the frequency bands actually used are the low band of 10 MHz to 770 MHz (962 MHz) and the high band of 1030 MHz to 3224 MHz. That is, the distributor according to the embodiment of the present invention only needs to operate at least in the low band of 10 MHz to 770 MHz and the high band of 1030 MHz to 3224 MHz. And, in the distributor according to the tenth embodiment of the present invention, the phase of the pass characteristic is mismatched in the usable frequency band of 10 MHz to 3224 MHz, but it operates well in the low band from 10 MHz to a predetermined lower limit frequency of the unused band, and in the high band from a predetermined upper limit frequency of the unused band to 3224 MHz. That is, the usable frequency band of the distributor according to the tenth embodiment of the present invention is substantially 10 MHz to 3224 MHz. [Explanation of symbols]

[0084] 1,2,3,4,200,300 distributor, 5 3 distributor, 6 4 distributor, 7 6 distributor, 8 8 distributor, 9 splitter, 11,21,31,41,201,301 Wilkinson 2-way splitter, 12,32,42,202,302 High-frequency transformer 2-way splitter, 14,15 splitter mixer, 91 directional coupling line splitter, 91a directional coupling line, 92 splitter transformer splitter, 92a splitter transformer, 93 attenuator, 100 building shared viewing system, 111a CATV station, 111b trunk equipment, 111c tap-off, 112 protection device, 113 BS / CS antenna, 114 mixer, 115 building amplifier, 116 distributor, 118 series unit, 2000 Wilkinson circuit, CS Distributor, T1 distribution transformer, T2 distribution transformer, T11 transformer, T12 transformer, W1,W2 distributed constant line, W11,W12 distributed constant line, W3,W4 distributed constant line

Claims

1. A distributor having a division number of 2, in which a high-frequency transformer 2-way distribution circuit and a Wilkinson 2-way distribution circuit are connected in parallel between an input terminal and an output terminal, the high-frequency transformer 2-way distribution circuit having a circuit configuration that functions equivalently as a low-pass filter between the input terminal and the output terminal; the Wilkinson 2-way distribution circuit having a circuit configuration that functions equivalently as a high-pass filter between the input terminal and the output terminal, A distributor characterized in that the Wilkinson 2-way distribution circuit is configured so that the phase of the pass characteristic of the high-pass filter lags the phase of the pass characteristic of the low-pass filter, thereby matching the phases of the pass characteristics of the low-pass filter and the high-pass filter, the outputs of the low-pass filter and the high-pass filter are frequency band synthesized, and the cutoff frequencies of the low-pass filter and the high-pass filter are approximately the same.

2. The distributor according to claim 1, characterized in that when the low-pass filter functions equivalently as a 4n-1 (n = 1, 2, 3, ...) stage T-type low-pass filter, the Wilkinson 2-way splitter is configured so that the high-pass filter functions equivalently as a 3-stage π-type high-pass filter, thereby matching the phases of the pass characteristics of the low-pass filter and the high-pass filter and synthesizing the frequency bands.

3. The distributor according to claim 1, characterized in that when the low-pass filter functions equivalently as a 4n+1 (n=1, 2, 3, . . .) stage T-type low-pass filter, the Wilkinson 2-way splitter is configured so that the high-pass filter functions equivalently as a 4n+3 (n=1, 2, 3, . . .) stage π-type high-pass filter, thereby matching the phases of the pass characteristics of the low-pass filter and the high-pass filter and synthesizing the frequency bands.

4. The distributor according to claim 1, characterized in that when the low-pass filter functions equivalently as a 4n+3 (n=1, 2, 3, . . .) stage T-type low-pass filter, the Wilkinson 2-way splitter is configured so that the high-pass filter functions equivalently as a 4n+1 (n=1, 2, 3, . . .) stage π-type high-pass filter, thereby matching the phases of the pass characteristics of the low-pass filter and the high-pass filter and synthesizing the frequency bands.

5. The distributor according to claim 1, characterized in that the high-frequency transformer 2-way split circuit is split into two by a splitter consisting of a primary coil and a secondary coil, and the Wilkinson 2-way split circuit is connected to the output terminals via a capacitor that makes it less susceptible to the resistance component that functions at low frequencies of the secondary coil.

6. 6. A splitter according to claim 1, wherein a frequency band of 10 MHz to 3224 MHz is obtained as a usable frequency band.

7. A divider having a division number of two, in which a high-frequency transformer two-way distribution circuit and a Wilkinson two-way distribution circuit are connected in parallel between an input terminal and an output terminal, and a predetermined frequency band including an unused frequency band is set as a usable frequency band, the high-frequency transformer 2-way distribution circuit having a circuit configuration that functions equivalently as a low-pass filter between the input terminal and the output terminal; the Wilkinson 2-way distribution circuit having a circuit configuration that functions equivalently as a high-pass filter between the input terminal and the output terminal, a cutoff frequency that is approximately matched between the low-pass filter and the high-pass filter is a predetermined frequency in the unused frequency band, and when the pass characteristics of the low-pass filter and the high-pass filter are in a phase mismatch state, the outputs of the low-pass filter and the high-pass filter are frequency band-combined.

8. The divider according to claim 1, characterized in that in the high-frequency transformer 2-way distribution circuit, the number of transformer turns is adjusted so that the distribution ratio is 2:1, and in the Wilkinson 2-way distribution circuit, a circuit configuration is adopted in which the distribution ratio is 2:1, thereby achieving a distribution ratio of 2:

1.

9. A power distribution system comprising a first distributor as claimed in any one of claims 1 to 4, and a second distributor and a third distributor as claimed in claim 6, a first output terminal of the first divider is connected to an input terminal of the second divider, and a second output terminal of the first divider is connected to an input terminal of the third divider; A distributor with a distribution ratio of 3, characterized in that an output terminal of the second distributor with a distribution ratio of 2 is a first output terminal, an output terminal of the second distributor with a distribution ratio of 1 and an output terminal of the third distributor with a distribution ratio of 1 are connected to form a second output terminal, and an output terminal of the third distributor with a distribution ratio of 2 is a third output terminal.

10. A power distribution system comprising a first distributor, a second distributor, and a third distributor, each of which is a distributor according to any one of claims 1 to 4, a first output terminal of the first divider is connected to an input terminal of the second divider, and a second output terminal of the first divider is connected to an input terminal of the third divider; A distributor having a distribution number of 4, characterized in that the two output terminals of the second distributor are a first output terminal and a second output terminal, and the two output terminals of the third distributor are a third output terminal and a fourth output terminal.

11. A fourth distributor as claimed in any one of claims 1 to 4, and a fifth distributor and a sixth distributor as claimed in claim 7, A first output terminal of the fourth divider is connected to an input terminal of the fifth divider, and a second output terminal of the fourth divider is connected to an input terminal of the sixth divider, A distributor having a division number of six, comprising three output terminals of the fifth distributor and three output terminals of the sixth distributor.

12. A seventh distributor which is the distributor according to any one of claims 1 to 4, and an eighth distributor and a ninth distributor which are the distributors according to claim 8, A first output terminal of the seventh distributor is connected to an input terminal of the eighth distributor, and a second output terminal of the seventh distributor is connected to an input terminal of the ninth distributor, A distributor having eight output terminals consisting of four output terminals of the eighth distributor and four output terminals of the ninth distributor, the distributor having a division number of eight.

13. A splitter in which a split transformer split circuit and a directional coupling line split circuit are connected in parallel between an input terminal, an output terminal, and a split terminal, the branch transformer branch circuit includes a branch transformer that branches a signal, and is configured to function equivalently as a T-type three-stage low-pass filter between the input terminal, the output terminal, and the branch terminal; the directional coupling line branch circuit includes a directional coupling line that branches a signal, the directional coupling line branch circuit being configured to function equivalently as a π-type three-stage high-pass filter between the input terminal, the output terminal, and the branch terminal; a branching circuit characterized in that the directional coupled line branching circuit is configured so that the phase of the pass characteristic of the high-pass filter lags the phase of the pass characteristic of the low-pass filter, thereby matching the phases of the pass characteristics of the low-pass filter and the high-pass filter, and the outputs of the low-pass filter and the high-pass filter are frequency band synthesized and output from the output terminal and the branching terminal, and the cutoff frequencies of the low-pass filter and the high-pass filter are approximately the same.

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