Method for transmitting microwave bits 1 in a carrier free interval following 2-4 wavelengths of the microwave carrier from an LTE or wimax station to a mobile terminal and data recovery using dpll at the mobile terminal

Abstract

To realize high-speed transmission of microwave radio.SOLUTION: When transmitting the microwave bit 1, the base station transmits an analog signal in which a carrier wave non-section corresponding to (m-k) (m: natural number power of 2) wavelengths continues after transmitting two to four wavelengths (k wavelengths) of the carrier wave. When a microwave bit 0 is transmitted, an analog signal of an m wavelength section carrier non-section is transmitted, and in a mobile terminal, from a signal when an output of a reception microwave reception method exceeds a selected threshold, an AND signal of a case where a counter value of a synchronization clock generation counter (85) of a counter value J * m that self-runs when there is no clear signal input and counts up by J times a clock of a carrier frequency is 0, 1, or (J * m-1) and a differential signal of rising of an input signal to an own digital PLL is generated, By clearing all the constituent flip-flops of the counter (85), clock synchronization with input data is performed, reproduced data is obtained, and fixed-length Ethernet frame synchronization is obtained from the reproduced data.SELECTED DRAWING: Figure 6

Description

[Technical Field]

[0001] The present invention relates to a high-speed wireless transmission method using microwaves.

[0002] In conventional LTE handovers (Non-Patent Document 1), data packets were transmitted after a wireless channel was selected, similar to IEEE802.11b handovers. Access from mobile nodes to LTE base stations was transmitted using CSMA / CD, which caused delays due to collisions. This limited the number of mobile terminals that could be switching LTE stations. After switching, communication took place using a time slot assigned to the channel, eliminating collisions like in CSMA / CD, and the number of channels was limited only by speed. In OFMDA of Non-Patent Document 1, the time frame for performing FFT is long, so harmonics higher than the fundamental wave are not generated.

[0003] Conventional wireless microwave signals are ON / OFF keyed microwave signals, as described in Non-Patent Document 2. The receiving side obtains the transmitted modulated data after low-pass filtering. [Prior art documents] [Non-patent literature]

[0004] [Non-Patent Document 1] M. Vijayalakshmi, et al. “A Cross Layer Scheduling Algorithm in IEEE 802.16e WiMAX Standard to Support RTPS Traffic Class”, 2014 fourth International Conference on Communication Systems and Network Technologies, 07-09 April 2014 [Non-patent document 2] Seymour Stein and J. Jey Jones, "Current Theory of Communication Lines," Morikita Publishing Co., Ltd., October 1970 Summary of the Invention [Problem to be solved by the invention]

[0005] Non-Patent Document 1 has the drawback of using CSMA / CD for LTE access in L2 handover when a mobile terminal accesses a new base station, resulting in long handover delays. OFMDA in Non-Patent Document 1 has the drawback that the sampling point for FFT cannot be determined when the mobile terminal moves at high speed, which can cause errors. Also, when there are a large number of subcarriers, the bandwidth used becomes too large to pass through the resonator. Also, since only two bits can be transmitted per 10 MHz subcarrier, high-speed bit transmission is not possible. Another drawback is that it is difficult to determine the boundaries of the FFT window frame at the mobile terminal.

[0006] As shown in Non-Patent Document 2, conventional ON / OFF keying uses a low-pass filter to regenerate signals, which has the drawback of not being able to transmit and receive high-speed data. Also, when sending bit 0, the carrier wave is turned off, which causes the signal to not pass smoothly through the carrier resonant circuit on the receiving side.

[0007] The object of this invention is to provide a wireless high-speed transmission method in which a microwave carrier is treated as an isolated wave, the carrier wave is ON / OFF modulated, sent to a mobile terminal, and data can be reproduced at the receiving end without using FFT. [Means for solving the problem]

[0008] The present invention has been made in consideration of the above-mentioned problems of the prior art, and the means of the present invention are shown in Aspects 1 to 5 of the present invention. A first aspect of the present invention is a wireless transmission method for transmitting and receiving a microwave 10 signal from an LTE or WiMAX base station to a mobile terminal, wherein the LTE or WiMAX base station, when transmitting microwave bit 1, transmits an analog signal in which a carrier is transmitted over two to four wavelengths (k wavelengths) followed by a carrier-free interval of (mk) wavelengths (m is a natural number power of 2), and when transmitting microwave bit 0, transmits microwave bit 1 or microwave bit 0 that transmits an analog signal in which a carrier-free interval is transmitted over m wavelength intervals, and transmits bit 1 or bit 0 of transmission data from an antenna to a mobile terminal, and the mobile terminal receives the microwave 10 signal received by the antenna using a microwave 10 signal receiving method, and reproduces bit 1 and bit 0 of the transmission data in clock synchronization using a digital PLL operation method from the signal when the output of the received microwave receiving method exceeds a threshold selected by a threshold determination method, thereby transmitting and receiving a microwave 10 signal that identifies an Ethernet frame, The digital PLL operation method is such that when there is no clear signal input, a synchronous clock generating counter (85) with a counter value J*m that counts up at J (J: natural number) times the clock of the carrier frequency, which runs free-running, clears all of the flip-flops constituting the counter (85) and inputs a set to a set-reset flip-flop (86) in response to an AND signal between the counter value J*m, which is 0, 1, or (J*m-1), and a differential signal of the rising edge of the input signal to the digital PLL, and the counter counts up at J times the clock of the carrier frequency. When the counter value of a synchronous clock generating counter (85) with a value J*m is (J*m / 2), the Q output of the set-reset flip-flop (86) is input to a D-type flip-flop (90), and then the set-reset flip-flop (86) is reset, and recovered data is obtained from the Q output of the D-type flip-flop (90), the clock is synchronized with the input data to recover data, and fixed-length Ethernet frame synchronization is obtained from the recovered data.

[0009] A second aspect of the present invention is a wireless transmission method for transmitting and receiving a microwave 10 signal from an LTE or WiMAX base station to a mobile terminal, wherein the LTE or WiMAX base station, when transmitting microwave bit 1, transmits an analog signal in which a carrier is transmitted for two to four wavelengths (k wavelengths) followed by a carrier-free interval of (mk) wavelengths, and when transmitting microwave bit 0, transmits an analog signal in which a carrier-free interval of m wavelengths is transmitted, transmits microwave bit 1 or microwave bit 0, and transmits bit 1 or bit 0 of transmission data from an antenna to a mobile terminal, and the mobile terminal receives the microwave 10 signal received by the antenna using a microwave 10 signal receiving method, and reproduces bit 1 and bit 0 of the transmission data in clock synchronization using a digital PLL operation method from the signal when the output of the received microwave receiving method exceeds a threshold selected by a threshold determination method, thereby transmitting and receiving a microwave 10 signal that identifies an Ethernet frame, The digital PLL operation method involves clearing all of the flip-flops of counter 3 with a high signal when the counter value of counter 3, which counts up at J times the carrier frequency clock and is free-running when there is no clear signal input, is 0 or 1 or (J*m-1), and inputting a set signal to set-reset flip-flop 1 and set-reset flip-flop 2 with an AND signal of a differential signal of the rising edge of the input signal to the digital PLL, and inputting a set signal to set-reset flip-flop 1 and set-reset flip-flop 2, and when set-reset flip-flop 1 is in the set state, inputting a clock of J times the carrier frequency, and clearing the count value of counter 1, which counts up at J times the carrier frequency, to a counter value of 4(=(J*m / 2)), latching the signal with a differential signal of the rising edge of the output of the counter 2, resetting the set-reset flip-flop 1 and resetting the set-reset flip-flop 2 with the differential signal, and immediately after the latching, setting all bits of the flip-flops of each stage of the counter 1 to 0, and stopping the input clock to the counter 1, and if the latched value exceeds a specified value 1, inputting a stuff clock to the counter 2, and if the latched value is less than a specified value 2 (<specified value 1-1), destuffing (excluding one clock) the input clock to the counter 2, synchronizing the clock with the input data, recovering the data, and obtaining fixed-length Ethernet frame synchronization from the recovered data.

[0010] A third aspect of the present invention is a wireless transmission method for transmitting and receiving a microwave 10 signal according to either the first or second aspect of the present invention, characterized in that the microwave 10 signal receiving method is a method in which a microwave 10 signal received by a single receiving antenna in a mobile terminal is received by a series LC resonator for each carrier frequency, and signals of carrier frequencies other than those required are dropped to earth, thereby passing through a signal of the required carrier frequency, amplifying it by a small amount, branching the output signal into two, delaying one of the two branches by one carrier wavelength, and superimposing it on the other of the two branches to add an analog signal and outputting the resulting voltage as an output signal.

[0011] A fourth aspect of the present invention is a wireless transmission method for transmitting and receiving microwave 10 signals according to either the first or second aspect of the present invention, characterized in that the microwave 10 signal receiving method in a mobile terminal is a method of receiving a microwave 10 signal via a single receiving antenna in a mobile terminal, dropping a signal of a high frequency carrier frequency at least twice the pass frequency to ground using a series RC filter at the base input of an npn bipolar transistor (221) for each carrier frequency, lowering the impedance of the pass frequency with a capacitor in a parallel RC filter between the emitter of the npn bipolar transistor (221) and ground, thereby increasing the current between the base and emitter of the pass frequency and increasing the current amplification factor, thereby passing a signal of a required carrier frequency, branching the output signal into two, delaying one of the two branches by one wavelength of the carrier wave, superimposing it on the other of the two branches, and outputting a voltage obtained by adding an analog signal to the output signal.

[0012] A fifth aspect of the present invention is a wireless transmission method for transmitting and receiving microwave 10 signals according to either the first or second aspect of the present invention, characterized in that the threshold determination method is a method in which a positive-phase voltage signal at the gate input of a PMOS transistor, the drain of which is connected to the drain of an NMOS with a constant output current on the side opposite to the side from which the output of the differential amplifier is extracted, raises the gate reference voltage threshold of the PMOS transistor, the drain of which is connected to the drain of an NMOS with a constant output current on the side from which the output of the differential amplifier to the DPLL is extracted, when the number of pulses of the drain output voltage to the DPLL of the PMOS on the side whose threshold is set at the gate exceeds 2 or is 2 or more in m carrier wavelength sections, and lowers the threshold when the number of pulses is 1 or less in a section that is I (I: natural number) times m carrier wavelength sections. [Effects of the Invention]

[0013] As explained above, the present invention involves extracting two to four microwave carrier wavelengths (k wavelengths), transmitting a signal followed by a carrier-free interval of (mk) wavelengths, and setting the transmitted data bit as 1, and setting the carrier-free interval of m wavelengths as 0. This signal is then transmitted from an LTE base station to a mobile terminal. At the mobile terminal, the microwave 10 signal received by a single receiving antenna is amplified slightly through a resonator for each carrier frequency, and when the output signal voltage exceeds the threshold selected by the threshold determination method, clock synchronization is performed using a digital PLL operation method to reproduce bits 1 and 0 of the transmitted data, thereby identifying the Ethernet frame. This method does not require a complex frame structure like existing OFDMA, but can be implemented using frequencies allocated to existing service providers, and has the advantage of enabling high-speed communication without using a low-pass filter on the receiving side to remove the carrier wave. Furthermore, the present invention has the advantage of being robust against fading, since the DPLL removes fading signals that exceed the input threshold. [Brief explanation of the drawings]

[0014] [Figure 1] FIG. 2 is a diagram showing the relationship between base stations, cells, and mobile terminals when a handover of a mobile terminal is performed between LTE (WIMAX) stations according to the first embodiment of the present invention. [Figure 2] FIG. 10 is a diagram for explaining an example of bit 1 transmission of transmission data at a microwave frequency that differs for each base station sent from an LTE station for base station selection when performing handover of a mobile terminal between LTE (WIMAX) stations in the first embodiment of the present invention. [Figure 3] FIG. 10 is a diagram for explaining an example of a bit 1 transmission circuit for transmission data of a microwave frequency that differs for each base station and is sent from an LTE station for base station selection when performing handover of a mobile terminal between LTE (WIMAX) stations in the first embodiment of the present invention. [Figure 4] FIG. 10 is a diagram for explaining an example of a bit 1 transmission circuit for transmission data of a microwave frequency that differs for each base station and is sent from an LTE station for base station selection when performing handover of a mobile terminal between LTE (WIMAX) stations in the first embodiment of the present invention. [Figure 5] FIG. 10 is a diagram illustrating an example of the operation of a circuit in which a microwave bit 1 signal transmitted from an LTE station in the first embodiment of the present invention is received by an antenna, branched into two, one of the branched signals delayed by one wavelength is added as an analog signal to the two branched signals with no delay, and an output signal of a superimposed signal is obtained. [Figure 6] FIG. 10 is a diagram illustrating an example of the operation of a circuit in which a microwave bit 1 signal transmitted from an LTE station in the first embodiment of the present invention is received by an antenna, branched into two, one of the branched signals delayed by one wavelength is added as an analog signal to the two branched signals with no delay, and an output signal of a superimposed signal is obtained. [Figure 7] FIG. 10 is a diagram illustrating an example of the operation of a differential amplifier circuit for generating a signal when the output signal of the superimposed signal exceeds a threshold, by passing through different resonators for each microwave frequency received by the antenna in the first embodiment of the present invention, branching into two, delaying one of the two branches by one wavelength, and adding the resulting signal as an analog signal to the two branches with no delay. [Figure 8]FIG. 10 is a diagram for explaining an example of the operation of a digital PLL that receives a signal that has passed through a different resonator for each microwave frequency received by the antenna in the first embodiment of the present invention and exceeds a threshold, and regenerates a received data clock. DETAILED DESCRIPTION OF THE INVENTION

[0015] A first embodiment of the present invention will be described with reference to Figures 1, 2, 3, 4, 5, 6, 7, and 8. Figure 1 shows the relationship between base stations, cells, and mobile terminals when a handover of a mobile terminal is performed between LTE (WIMAX) stations, and in Figure 1, 1 is a source base station A, 2 is a destination base station B, 3 is another base station C, 4 is the mobile terminal, 5 is the cell of base station A, 6 is the cell of base station B, and 7 is the cell of base station C.

[0016] The operation of Fig. 1 will be explained below. Fig. 1 is a diagram showing the relationship between base stations, cells and mobile terminals when a handover of a mobile terminal between LTE (WIMAX) stations is performed. When a handover in the radio domain between LTE stations is performed, a mobile terminal (4) connected to a source LTE station A (1) approaches a destination base station B (2). The mobile terminal selects microwaves received by the antenna using a plurality of resonators, recovers clock from one of the selected signals using a DPLL shown in Fig. 4 to recover transmission data, identifies a frame, and if the base station MAC address in the frame header is equal to the MAC address of the destination base station advertised by the source base station in communication, the base station of the carrier frequency passing through that resonator is determined to be a candidate for the destination base station, and the source LTE station A (1) is notified of the base station M The source base station A (1) determines the NIC MAC address of the destination base station B (2) from the base station MAC address sent from the mobile terminal (4), and sends a handover command packet addressed to the destination base station B (2) via a MAC ring network, MAC tree network, or IP network with the NIC MAC address as the destination MAC address. When the frame or packet arrives at the destination base station B (2), the destination base station B (2) determines a channel to the mobile terminal and notifies the mobile terminal (4) of the channel number. If a response is received from the mobile terminal (4), the destination base station B (2) sends a frame addressed to the mobile terminal (4) via the channel. Alternatively, the mobile terminal that received the channel number sends the first packet after handover to the destination base station.

[0017] Next, let's look at Figure 2. Figure 2 illustrates how bit 1 of the transmission data is transmitted on a carrier wave with a different carrier frequency for each base station sent from an LTE station to select a base station when a mobile terminal handovers between LTE (WIMAX) stations. Figure (a) shows an example in which the LTE station transmits a microwave carrier bit 1 with a carrier-free interval of four wavelengths (mk) (where m is 2) after the signal extracted from a four-wavelength (k wavelength) carrier oscillator corresponding to bit 1 of the transmission data. Figure (b) shows an example of a signal obtained by receiving the signal in Figure (a) at the receiver, splitting the received signal into two, delaying one of the signals by one carrier wavelength, and superimposing it on the other received signal as an analog signal, and then adding them together. The amplitude is doubled over the three-wavelength interval. This is resistant to fading because even if one wavelength is lost due to fading, one wavelength of doubled amplitude remains.

[0018] Next, we will explain the microwave modulation circuit of the LTE station in Figure 3. In Figure 3, 120 is a carrier oscillator, 122 is a common-emitter npn bipolar transistor, 124 is a common-source NMOS transistor with negative feedback from drain to gate, 126 is a high-output emitter-follower npn bipolar transistor, 127 is a coaxial cable leading to the antenna, 132 is a binary counter that counts up using a differential signal of the rising edge of the output signal of 120, 133 is a circuit that outputs a clock of two differential signals, the rising and falling edges of the output signal of counter 132, 134 is a signal (H cut down) transmission circuit that outputs a microwave bit 1 with four wavelengths of no carrier interval (low level) after a virtual bit 1 (high level) of four wavelengths corresponding to bit 1 of the transmitted data, or a microwave bit 0 (low level) with eight carrier wavelengths of no interval, 137 is an inverted signal of the 10 signal that is high only during the H cut down of 134 and low otherwise, and 129 is a transfer gate.

[0019] Next, the operation of Figure 3 will be explained. The output of oscillator 120 is supplied to the base of bipolar transistor 122 and sent to circuit 132. The collector output of bipolar transistor 122 is AC-connected to ground via a capacitor by transfer gate 129, which is gate-on controlled by an H-bar signal of control signal 137, and is blocked from passing through. During other times when the transfer gate is off, only the four-carrier wavelength section of bit 1 of the transmitted data (the upper wave in Figure 2) passes through and is input to the gate of NMOS 124. The drain output of NMOS 124 is input to the base of high-output bipolar transistor 126 via a capacitor of about 1000 pF (picofarads), and is supplied as the emitter output between ground and the transmitting antenna via coaxial cable 127.

[0020] Next, the operation of Fig. 4 will be described. In Fig. 4, 120 is an oscillator of carrier frequency f, 121 is a sampling circuit, 122 is an AD conversion circuit, 123 is a circuit that discards AD digital values ​​outside the time frame of carrier 2 or 4 wavelengths, 124 is a circuit that performs FFT conversion of the time frame of 2 or 4 wavelengths, 125 is a circuit that removes harmonics of 2f or higher of the fundamental wave f, 126 is a circuit that performs IFFT conversion of the FFT signal from which harmonics of 2f or higher have been removed, 127 is a digital signal storage memory for a 2 or 4 wavelength provisional bit 1 waveform that stores the output of 126 only once, 130 is a transmission control signal transmission circuit that outputs microwave bit 1 in a 2 or 4 wavelength carrier-free section after provisional bit 1 of carrier 2 or 4 wavelengths, or microwave bit 0 in a 4 or 8 wavelength carrier-free section, and 128 is a DA conversion circuit whose output is connected to an antenna driver. In FIG. 3, the output signal of oscillator 120 of carrier frequency f is sampled in sampling circuit 121 with a clock of 8 times or more f, then converted into a multi-value digital signal in AD conversion circuit 122, AD digital values ​​outside the time frame of carrier 2 or 4 wavelengths are discarded in 123, only the time frame of 2 or 4 wavelengths is FFT transformed in 124, harmonics of fundamental wave f of 2f or more are removed in 125, the FFT signal from which harmonics of 2f or more have been removed is IFFT transformed in 126, the output of 126 is stored in a digital signal storage memory of a provisional bit 1 waveform of 2 or 4 wavelengths which stores the signal only once, and the signal is repeatedly read out from memory 127 by a transmission control signal of provisional bit 1 of carrier 2 or 4 wavelengths followed by microwave bit 1 of 2 or 4 wavelengths with no carrier section, or microwave bit 0 of 4 or 8 wavelengths with no carrier section in 130, and the output of 128 is converted into an analog signal by a DA conversion circuit connected to the antenna driver. The digital signal storage memory for the 127 two-wavelength or four-wavelength provisional bit-one waveform may store two or four wavelengths of the carrier wave as is without removing the harmonics by FFT or IFFT.

[0021] Next, the operation will be described with reference to Fig. 5. Fig. 5 shows an example of a circuit of a mobile terminal that receives microwave bit 1 and microwave bit 0 transmitted from an LTE station. In Figure 5, 20 is an antenna, 21 is an NMOS transistor that forms a circuit with a series LC resonator that drops signals of carrier frequencies f1 and f2 other than the desired one to ground, 22 and 23 are npn bipolar transistors, 24, 25, and 27 are npn bipolar transistors, 26 is a delay coaxial cable, R1, R2, R3, R4, R5, R6, R7, R8, and R9 are resistors, c, c20, and c21 are capacitors, L20 and L21 are coils, 28 is another branch signal line, 29 is an input signal to the bases of npn bipolar transistors 22 and 23, and 30 is the output signal of npn bipolar transistor 27.

[0022] Next, the operation of Figure 5 will be explained. The carrier wave received by antenna 20 is branched for each NMOS transistor that constitutes an LC resonator that drops non-target carrier frequencies f1 and f2. f1 = 1 / (2pai√(L20 * c20), and to improve transmission, L, which determines the time constant, is made small. Resistors may be added to this LC resonator. The collector output signal of NMOS transistor 21 is input to the bases of bipolar transistors 22 and 23, and the emitter output of bipolar transistor 22 is input to coaxial cable 26, which has an input impedance of 50 Ω. The input signal is delayed by one carrier wavelength on coaxial cable 26 and flows through resistor R1, which has a 50 Ω termination resistance. The voltage across resistor R1 becomes the base current of npn bipolar transistor 24. The collector current of npn bipolar transistor 24 flows in parallel through resistors R3, R5, and R4. Meanwhile, the emitter output of bipolar transistor 23 is input without delay to the base of npn bipolar transistor 25, and the collector output AC A signal flows in parallel through resistors R3, R4, and R5. Resistor R5 is the sum of the currents from the collectors of npn bipolar transistors 24 and 25, so a sum current proportional to the voltage across resistor R5 flows through the base of npn bipolar transistor 27. An amplified sum current flows through the collector of npn bipolar transistor 27. Therefore, the collector voltage of npn bipolar transistor 27, indicated by 30 in the figure, overlaps over three wavelengths, doubling its amplitude. The doubled voltage is sent to FIG. 6 as bit 1, and signals above the threshold are sent to the DPPL in FIG. 8 using the threshold determination method in FIG. 7. Reference numeral 29 in the figure represents the antenna reception signal input to the bases of bipolar transistors 22 and 23, and is the signal in FIG. 2(a).

[0023] Next, the operation will be described with reference to Fig. 6. Fig. 6 shows another example of a circuit of a mobile terminal that receives microwave bit 1 and microwave bit 0 transmitted from an LTE station.

[0024] In Figure 6, 20 is an antenna, 221 is an npn bipolar transistor that constitutes a frequency filter, 22 and 23 are npn bipolar transistors, 24, 25, and 27 are npn bipolar transistors, 26 is a delay coaxial cable, R1, R2, R3, R4, R5, R6, R7, R8, R20, and R21 are resistors, c, c20, and c21 are capacitors, 28 is another branch signal line, 29 is an input signal to the bases of npn bipolar transistors 22 and 23, and 30 is the output signal of npn bipolar transistor 27.

[0025] Next, the operation of Figure 6 will be explained. The carrier wave received by antenna 20 is branched by each npn bipolar transistor that constitutes the frequency filter. npn bipolar transistor 221 that constitutes the frequency filter drops frequency signals that are approximately twice as high as the selected frequency using a resistor R20 of approximately 1000 Ω at the base input point and capacitor C20 of approximately pF (picofarads). Resistor 21 and capacitor 21 at the emitter of npn bipolar transistor 221 that constitute the frequency filter reduce the impedance of capacitor 21 for frequencies above the selected frequency, increasing the current flowing through capacitor 21 between the base and emitter, and increasing the current amplification of the selected frequency. The npn bipolar transistors that constitute the frequency filters for other branch signals have a higher selected frequency than transistor 221, so the frequencies dropped by resistor R20 and capacitor C20 are higher than those of transistor 221, and the pass frequencies of resistors corresponding to resistor 21 and capacitor 20 are also higher than those of transistor 221. The collector output signal of npn transistor 221, which constitutes a frequency filter, is input to the bases of bipolar transistors 22 and 23, and the emitter output of bipolar transistor 22 is input to coaxial cable 26, which has an input impedance of 50 Ω. The input signal is delayed by one carrier wavelength on coaxial cable 26 and flows through resistor R1, which has a 50 Ω termination resistance. The voltage across resistor R1 becomes the base current of npn bipolar transistor 24. The collector current of npn bipolar transistor 24 flows in parallel through resistors R3, R5, and R4. Meanwhile, the emitter output of bipolar transistor 23 is input without delay to the base of npn bipolar transistor 25, and the collector output AC signal flows in parallel through resistors R3, R4, and R5. Since the sum of the currents from the collectors of npn bipolar transistors 24 and 25 flows through resistor R5, a sum current proportional to the voltage across resistor R5 also flows through the base of npn bipolar transistor 27. An amplified current of the sum of the base currents flows through the collector of npn bipolar transistor 27.Therefore, the collector voltage of npn bipolar transistor 27 shown in 30 in the figure overlaps over three wavelength sections, doubling the amplitude, and the doubled section is set as bit 1, and a signal above the threshold is sent to DPPL in FIG. 8 using the threshold determination method in FIG. 7. 29 in the figure is the antenna received signal input to the bases of bipolar transistors 22 and 23, and is the signal shown in FIG. 2(a).

[0026] Next, an example of the operation of the differential amplifier circuit for generating a signal when a signal received by the antenna of the first embodiment of the present invention passes through a different resonator for each microwave frequency and exceeds a threshold will be described with reference to Fig. 7. In Fig. 7, 300 denotes a signal received by the antenna of a mobile terminal or tablet and passes through a different resonator for each microwave frequency, 301 and 302 denote PMOS transistors whose drains are connected to the drain of the NMOS transistor 303 via the same resistor 22, and 305 denotes an output signal directed to the DPLL of Fig. 10.

[0027] Next, the operation of Figure 7 will be described. A DC voltage lower than the power supply voltage, determined by the ratio of the resistance values ​​of resistors R20 and R21, is applied to the gate of PMOS 301, turning PMOS 301 ON. A fixed voltage is applied between the gate and source of NMOS 303, and a constant current flows from the drain to the source of NMOS 303. When a positive-phase signal is input that has passed through a different resonator for each microwave frequency received by the antenna of the mobile terminal or tablet 300, an AC component is applied to the gate of PMOS 301 through resistors 20 and 21. Resistor 23, which has a smaller resistance than resistors 20 and 21 for the DC component, drops the voltage from the power supply voltage and inputs it to the gate of PMOS 301. When the peak voltage of the input voltage is higher than the threshold voltage of the gate of PMOS 302, PMOS 301 is turned off and PMOS 302 is turned on, causing the output voltage of 305 to go from low due to the voltage drop across resistor R22 when PMOS 301 is turned on to high due to the positive power supply voltage. Therefore, by controlling the threshold voltage so that the time it takes for the output voltage of 305 to go from low to high is minimized, only bit 1 of the transmitted data becomes a high signal. This eliminates fading signals with voltages lower than bit 1 of the transmitted data, and the high signal output from 305 is not affected by fading. The threshold voltage is raised when the output voltage pulse of 305 exceeds 2 or is equal to or greater than 2 within n (n: k (e.g., 2) times J (J: an integer multiple of 2, for example)) carrier wavelength intervals, and lowered when the output voltage pulse is less than 1 or 0 within m (m: a natural number) times n carrier wavelength intervals. The threshold voltage may be a signal obtained by DA converting the threshold level. Figure 9 shows the case where a signal obtained by delaying the transmission signal in Figure 3 and adding an analog signal is input, and the case where a signal obtained by receiving the transmission signal in Figure 4 by an antenna and passing through a resonator is slightly amplified is input.

[0028] Next, we will explain Figure 8. Figure 8 is an example of a digital PLL (DPLL) built into a mobile or tablet terminal, where the system clock is J times the 2.4G frequency, which is about the 4G microwave carrier frequency. Figure 8 shows an example where transmission bit 1 with k=3 is sent over three wavelengths. On the receiving side, the threshold is exceeded by one or both of the two overlapping wavelengths. In FIG. 8, 102 is an input signal (output signal 305 in FIG. 6) of a signal that is selected by a mobile terminal using a plurality of resonators from microwaves received by the antenna, and one of the selected signals exceeds a threshold; 31 is a differentiation circuit for the rising edge of the input signal 102; 80 is a system clock (a clock J times the carrier frequency clock f); 85 is a synchronous clock generation counter ((J*8) counter) that counts up with a clock J times the carrier frequency f and runs free if there is no clear input signal; 35 is an AND circuit that outputs a signal to clear all flip-flops constituting counter 85 by ANDing high signal 39 and the high output signal of differentiation circuit 31 when the counter value of counter 85 is 0 or 1 or (J*8-1); 32 is a When the value is (J*8-1), an AND circuit outputs a signal to set the set-reset flip-flop 86 by ANDing the high signal 39 and the high output signal of the differentiation circuit 31; 38 is a high signal when the counter value of the counter 85 is (J*8 / 2); signal 38 inputs the Q output of the set-reset flip-flop 86 to a D-type flip-flop 90, and the differentiated signal of the output of the delay circuit 37 of signal 38 resets the set-reset flip-flop 86; 91 is the reproduced data of the Q output of the D-type flip-flop; and 92 is a fixed-length Ethernet frame synchronization circuit.

[0029] Next, the operation of Figure 8 will be described. When the output of the differentiation circuit 31 becomes 1 (High) and the counter value of the counter 85 is 0, 1, or a high signal 39 when (J*m-1) (=(J*m-1)), a set signal is input to the set / reset FF2 (86), and all flip-flops constituting the counter 85 are cleared. When the phase of the input data leads the clock phase of J*f, the counter 85 normally clears from a state where it was cleared at counter 0 to a state where it is cleared at counter value 1. Conversely, when the phase of the input data lags the clock phase of J*f, the counter 85 normally clears from a state where it was cleared at counter 0 to a state where it is cleared at counter value (J*m-1). The Q output of the set / reset flip-flop 86 is input to a D-type flip-flop 90 according to the counter value (J*m / 2) of the counter 85, and the Q output becomes the recovered data 91. Because the recovered data contains bit errors, a fixed-length Ethernet frame synchronization circuit 92 with a synchronization protection circuit is required. Frame synchronization is achieved by the delimiter before the frame. In this way, the output signal of the synchronous clock generating asynchronous counter 85 is synchronized with the clock component of the input signal. When a crystal oscillator is used, the accuracy of the mobile terminal's system clock is approximately 10-6, which is J*1000 times different from a clock with a carrier frequency of J times 2.4 GHz, resulting in a deviation of J*1000 clocks per second. In other words, the counter 85's clear signal changes from a counter value of 0 to a value of 1 or (J*8-1) J times per ms. The phase deviation due to the movement of a mobile terminal, in the case of a car traveling at 100 km / h, is 3 cm per ms. This means that 2.5 cm, which is 1 / J (=4) of the 2.4 GHz wavelength of 10 cm, is corrected once per ms due to the crystal oscillator error. Therefore, the phase correction due to movement and the phase correction due to the crystal oscillator error are comparable. Unlike OFMDA, FIG. 8 has the advantage of enabling high-speed transmission because it quickly corrects the phase shift of the synchronous clock caused by the movement of the mobile terminal. The mobile terminal identifies an Ethernet frame from the reproduced data in Figure 8, reads the base station MAC address from the frame header, and if the MAC address is equal to the MAC address of a neighboring base station advertised by the source base station, sends the base station MAC address to the source base station as the MAC address of a candidate destination base station. [Explanation of symbols]

[0030] 1. Source base station A 2 Destination base station B 3. Other base station C 4. Mobile terminals 5 Base station A's cell 6 Base station B cell 7 Base station C cell

Claims

1. A wireless transmission method for transmitting and receiving a microwave 10 signal from an LTE or WiMAX base station to a mobile terminal, wherein the LTE or WiMAX base station, when transmitting a microwave bit 1, transmits a carrier wave for two to four wavelengths (k wavelengths) and then transmits an analog signal followed by a carrier-free interval of (m-k) wavelengths (m: a natural number power of 2), and when transmitting a microwave bit 0, transmits a microwave bit 1 or microwave bit 0 that transmits an analog signal with a carrier-free interval of m wavelengths, and transmits bit 1 or bit 0 of transmission data from an antenna to a mobile terminal, and the mobile terminal receives the microwave 10 signal received by the antenna using a microwave 10 signal receiving method, and reproduces bit 1 or bit 0 of the transmission data in clock synchronization using a digital PLL operation method from the signal when the output of the received microwave receiving method exceeds a threshold selected by a threshold determination method, thereby transmitting and receiving a microwave 10 signal that identifies an Ethernet frame; The digital PLL operation method is characterized in that when a clear signal is not input, a synchronous clock generating counter (85) with a counter value J*m, which counts up at J times the clock of the carrier frequency (J: natural number), and when the counter value is 0, 1, or (J*m-1), all flip-flops constituting the counter are cleared with an AND signal of a differential signal of the rising edge of an input signal to the digital PLL, and a set input is made to a set-reset flip-flop (86); when the counter value of the synchronous clock generating counter (85) with a counter value J*m, which counts up at J times the clock of the carrier frequency, is (J*m / 2), a Q output of the set-reset flip-flop (86) is input to a D-type flip-flop (90), and then the set-reset flip-flop (86) is reset, and recovered data is obtained from the Q output of the D-type flip-flop (90); data is recovered in clock synchronization with the input data, and fixed-length Ethernet frame synchronization is obtained from the recovered data. A wireless transmission method for transmitting and receiving microwave 10 signals.

2. A wireless transmission method for transmitting and receiving a microwave 10 signal from an LTE or WiMAX base station to a mobile terminal, wherein the LTE or WiMAX base station, when transmitting a microwave bit 1, transmits an analog signal in which a carrier is transmitted for two to four wavelengths (k wavelengths) followed by a carrier-free interval of (m-k) wavelengths, and when transmitting a microwave bit 0, transmits an analog signal in which a carrier-free interval of m wavelengths is transmitted, transmits microwave bit 1 or microwave bit 0, and transmits bit 1 or bit 0 of transmission data from an antenna to a mobile terminal, and the mobile terminal receives the microwave 10 signal received by the antenna using a microwave 10 signal receiving method, and reproduces bit 1 or bit 0 of the transmission data in clock synchronization using a digital PLL operation method from the signal when the output of the received microwave receiving method exceeds a threshold selected by a threshold determination method, thereby transmitting and receiving a microwave 10 signal that identifies an Ethernet frame; The digital PLL operation method is as follows: when the counter value of counter 3, which is free-running when there is no clear signal input and has a counter value J*m that counts up at J times the clock of the carrier frequency, is 0, 1, or (J*m-1), a high signal is output and an AND signal of a differential signal of the rising edge of the input signal to the digital PLL is generated; all of the flip-flops of counter 3 are cleared; and a set input is input to set-reset flip-flop 1 and set-reset flip-flop 2; when set-reset flip-flop 1 is in a set state, a clock of J times the carrier frequency is input; and the count value of counter 1, which counts up with the clock, is input to synchronous clock generating counter 2, which counts up with the clock of J times the carrier frequency and has an upper limit counter value of (J*m-1). a differential signal of the rising edge of the output of the counter 2 when the counter value is 4 (=(J*m / 2)), the differential signal is used to reset the set-reset flip-flop 1 and the set-reset flip-flop 2; immediately after the latching, all bits of the flip-flops in each stage of the counter 1 are set to 0, and the input clock to the counter 1 is stopped; if the latched value exceeds a specified value 1, a stuff clock is input to the counter 2; if the latched value is less than a specified value 2 (<specified value 1-1), the input clock to the counter 2 is destuffed (one clock is removed), the clock is synchronized with the input data, the data is reproduced, and fixed-length Ethernet frame synchronization is obtained from the reproduced data. A wireless transmission method for transmitting and receiving microwave 10 signals.

3. The microwave 10 signal receiving method is a method in which, in a mobile terminal, a microwave 10 signal received by a single receiving antenna is received using a series LC resonator for each carrier frequency, and signals of carrier frequencies other than the required one are dropped to earth, so that the signal of the required carrier frequency is passed through and slightly amplified, the output signal is branched into two, one of the two branches is delayed by one wavelength of the carrier wave, and the output signal is superimposed on the other of the two branches and an analog signal is added to the delayed signal, resulting in a voltage being output as an output signal.

4. The microwave 10 signal receiving method is a wireless transmission method for transmitting and receiving microwave 10 signals according to claim 1 or 2, characterized in that in a mobile terminal, a microwave 10 signal received by a single receiving antenna is filtered by a series RC filter at the base input of an npn bipolar transistor (221) for each carrier frequency, and a signal of a high frequency carrier frequency at least twice the pass frequency is dropped to ground, and a parallel RC filter is used between the emitter of the npn bipolar transistor (221) and ground to lower the impedance of the pass frequency with a capacitor, thereby increasing the current between the base and emitter of the pass frequency and increasing the current amplification factor, and the signal of the required carrier frequency is passed through, the output signal is branched into two, one of the two branches is delayed by one wavelength of the carrier wave, and the other of the two branches is superimposed on the other branch and an analog signal is added to it, resulting in a voltage being output as an output signal.

5. 3. The wireless transmission method for transmitting and receiving microwave 10 signals according to claim 1, wherein the threshold determining method is a method of raising a gate reference voltage threshold of a PMOS transistor whose drain is connected to the drain of an NMOS with a constant output current on the side opposite to the side from which the output of the differential amplifier is taken out, when the number of pulses of the drain output voltage to the DPLL of the PMOS on the side whose threshold is set at the gate exceeds 2 or is 2 or more in m carrier wavelength sections, and lowering the threshold when the number of pulses is 1 or less in a section of I (I: natural number) times m carrier wavelength sections.

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