Electronic atomization apparatus and control method

Abstract

Provided in the present application are an electronic atomization apparatus and a control method. The electronic atomization apparatus comprises: a susceptor, which is used for heating an aerosol-generating substrate to generate an aerosol; an LC oscillator, which comprises an inductor coil and a capacitor, and is configured to guide an alternating current to flow through the inductor coil, and then drive the inductor coil to provide energy to the susceptor, such that the susceptor heats the aerosol-generating substrate; and a controller, which is configured to drive the LC oscillator by means of a PWM control signal to form the alternating current that flows through the inductor coil, and is configured to measure the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal, and adjust the frequency of the PWM control signal, such that the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is kept at a predetermined threshold. In the electronic atomization apparatus, the frequency of the PWM control signal is adjusted by means of monitoring the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal, such that the LC oscillator keeps operating in the maximum resonant state.

Description

Electronic atomization device and control method

[0001] CROSS-REFERENCE TO RELATED APPLICATIONS

[0002] This application claims priority to the Chinese patent application No. 202410856961.6, filed on June 27, 2024, and entitled “Electronic atomization device and control method”, the content of which is incorporated herein by reference in its entirety. TECHNICAL FIELD

[0003] The present application relates to the technical field of electronic atomization, and in particular to an electronic atomization device and a control method. BACKGROUND

[0004] Tobacco products, such as cigarettes, cigars, and the like, burn tobacco during use to produce tobacco smoke. Attempts have been made to provide alternatives to these burning tobacco products by creating products that release compounds without burning.

[0005] Examples of such products are heat-not-burn devices that release compounds by heating, rather than burning, a material. For example, the material can be tobacco or other non-tobacco products, which can or can not contain nicotine. As another example, there are aerosol provision devices, such as so-called electronic atomization devices. These devices typically contain a liquid that is heated to cause it to vaporize, thereby producing an aerosol that can be inhaled. Known electronic atomization devices, by LC oscillator oscillation to form an alternating current flowing through the inductor coil to cause the inductor coil to generate a varying magnetic field to induce the susceptor heating aerosol provision device to generate an aerosol, and by detecting the peak value of the resonant voltage of the inductor coil, etc. to determine the shift of the optimum resonant frequency caused by the susceptor heating, thereby adjusting the working frequency of the LC oscillator to make the LC oscillator work in the maximum resonance state.

[0006] SUMMARY

[0007] One embodiment of the present application provides an electronic atomization device, comprising:

[0008] a susceptor for heating an aerosol generating substrate to generate an aerosol;

[0009] an LC oscillator comprising an inductor coil and a capacitor; the LC oscillator is configured to direct an alternating current to flow through the inductor coil, and in turn drive the inductor coil to provide energy to the susceptor to heat the aerosol generating substrate;

[0010] a controller configured to:

[0011] drive the LC oscillator to form the alternating current flowing through the inductor coil with the PWM control signal, and detect the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal;

[0012] adjusting the frequency of the PWM control signal to keep the phase difference between the resonant voltage or current of the LC oscillator and the PWM control signal at a predetermined threshold.

[0013] In some embodiments, the controller is configured to adjust the frequency of the PWM control signal to keep the phase difference between the resonant voltage of the LC oscillator and the PWM control signal at zero or close to zero.

[0014] In some embodiments, the controller is further configured to:

[0015] determining the optimal resonant frequency of the LC oscillator according to the phase difference between the resonant voltage or current of the LC oscillator and the PWM control signal being the predetermined threshold;

[0016] determining the temperature of the susceptor according to the optimal resonant frequency of the LC oscillator.

[0017] In some embodiments, determining the temperature of the susceptor according to the optimal resonant frequency of the LC oscillator comprises:

[0018] determining the actual inductance value of the inductor coil in operation according to the optimal resonant frequency of the LC oscillator, and determining the temperature of the susceptor according to the actual inductance value.

[0019] In some embodiments, the controller is further configured to:

[0020] determining the optimal resonant frequency of the LC oscillator according to the phase difference between the resonant voltage or current of the LC oscillator and the PWM control signal being the predetermined threshold;

[0021] adjusting the frequency of the PWM control signal to keep the frequency of the PWM control signal the same or close to the optimal resonant frequency of the LC oscillator.

[0022] In some embodiments, further comprising:

[0023] a phase difference detection module for detecting the phase difference between the resonant voltage or current of the LC oscillator and the PWM control signal; the phase difference detection module comprises:

[0024] a waveform converter for converting the resonant voltage or current of the LC oscillator into a square wave signal; the square wave signal has the same frequency and phase as the resonant voltage or current of the LC oscillator;

[0025] the phase difference detection module detects the phase difference by comparing the square wave signal and the PWM control signal.

[0026] In some embodiments, the waveform converter comprises a high-speed comparator or a zero-crossing comparator.

[0027] In some embodiments, the phase difference detection module further comprises:

[0028] a time-to-digital converter chip for calculating a time difference between the square wave signal and the PWM control signal; and

[0029] or a phase comparator chip for comparing a phase difference between the square wave signal and the PWM control signal, thereby obtaining the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal.

[0030] In some embodiments, the controller is further configured to prevent or interrupt the LC oscillator from directing the alternating current to flow through the inductor coil when determining that the temperature of the susceptor exceeds a predetermined threshold.

[0031] In some embodiments, the controller is further configured to determine the puffing action of the user according to a change in the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal.

[0032] Yet another embodiment of the present application also proposes an electronic atomization device, comprising:

[0033] a susceptor for heating an aerosol generating substrate to generate an aerosol;

[0034] an LC oscillator comprising an inductor coil and a capacitor; the LC oscillator is configured to direct an alternating current to flow through the inductor coil, thereby driving the inductor coil to provide energy to the susceptor to heat the aerosol generating substrate;

[0035] a controller configured to:

[0036] drive the LC oscillator with a PWM control signal to form the alternating current flowing through the inductor coil, and detect a phase difference between a resonant voltage or resonant current of the LC oscillator and the PWM control signal;

[0037] determine an optimal resonant frequency of the LC oscillator according to the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal, and determine a temperature of the susceptor according to the optimal resonant frequency of the LC oscillator.

[0038] In some embodiments, determining the temperature of the susceptor according to the optimal resonant frequency of the LC oscillator comprises:

[0039] determining an actual inductance value of the inductor coil in operation according to the optimal resonant frequency of the LC oscillator, and determining the temperature of the susceptor according to the actual inductance value by looking up a table or calculation.

[0040] Yet another embodiment of the present application also proposes an electronic atomization device, comprising:

[0041] a susceptor for heating an aerosol generating substrate to generate an aerosol;

[0042] an LC oscillator comprising an inductor and a capacitor; the LC oscillator is configured to direct an alternating current to flow through the inductor, and in turn drive the inductor to provide energy to the susceptor to heat the aerosol generating substrate;

[0043] a controller configured to:

[0044] drive the LC oscillator with a PWM control signal having a given reference frequency to form the alternating current flowing through the inductor, and detect a phase difference between a resonant voltage or current of the LC oscillator and the PWM control signal;

[0045] adjust a frequency of the PWM control signal, and update the reference frequency with a current frequency of the PWM control signal when the phase difference is a predetermined threshold;

[0046] control the LC oscillator to start operating according to the updated reference frequency to start heating the susceptor.

[0047] Yet another embodiment of the present application also proposes a control method of an electronic atomization device, the electronic atomization device comprising:

[0048] a susceptor for heating an aerosol generating substrate to generate an aerosol;

[0049] an LC oscillator comprising an inductor and a capacitor; the LC oscillator is configured to direct an alternating current to flow through the inductor, and in turn drive the inductor to provide energy to the susceptor to heat the aerosol generating substrate;

[0050] the method comprising:

[0051] driving the LC oscillator with a PWM control signal to form the alternating current flowing through the inductor, and detecting a phase difference between a resonant voltage or current of the LC oscillator and the PWM control signal;

[0052] adjusting a frequency of the PWM control signal to keep the phase difference between the resonant voltage or current of the LC oscillator and the PWM control signal at a predetermined threshold.

[0053] Yet another embodiment of the present application also proposes a control method of an electronic atomization device, the electronic atomization device comprising:

[0054] a susceptor for heating an aerosol generating substrate to generate an aerosol;

[0055] an LC oscillator comprising an inductor and a capacitor; the LC oscillator is configured to direct an alternating current to flow through the inductor, and in turn drive the inductor to provide energy to the susceptor to heat the aerosol generating substrate;

[0056] the method comprising:

[0057] The LC oscillator is driven by the PWM control signal to form an alternating current flowing through the inductor, and the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is detected;

[0058] The optimum resonant frequency of the LC oscillator is determined according to the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal, and the temperature of the susceptor is determined according to the optimum resonant frequency of the LC oscillator.

[0059] The above electronic atomization device adjusts the frequency of the PWM control signal by monitoring the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal, so that the LC oscillator can work in the maximum resonant state. BRIEF DESCRIPTION OF DRAWINGS

[0060] One or more embodiments are illustrated by way of example in the figures that form a part of this patent document, these illustrative examples do not limit the embodiments, and elements having the same reference numerals designate like elements throughout the various figures, unless otherwise indicated, the figures in the drawings are not necessarily to scale.

[0061] FIG. 1 is a schematic diagram of an electronic atomization device according to an embodiment;

[0062] FIG. 2 is a structural block diagram of an embodiment of the circuit in FIG. 1;

[0063] FIG. 3 is a schematic diagram of the basic components of an embodiment of the circuit in FIG. 2;

[0064] FIG. 4 is a schematic diagram of another embodiment of the phase difference detection module in FIG. 2;

[0065] FIG. 5 is a schematic diagram of a correlation curve between the actual inductance value of the inductor of the susceptor of the 185 permalloy measured in an embodiment and the heating temperature of the susceptor;

[0066] FIG. 6 is a schematic diagram of a comparison between the resonant voltage Vr and the PWM control signal Vp when the optimum resonant frequency of the LC oscillator is the same as the frequency of the PWM control signal in an embodiment;

[0067] FIG. 7 is a schematic diagram of a comparison between the resonant voltage Vr and the PWM control signal Vp when the optimum resonant frequency of the LC oscillator is different from the frequency of the PWM control signal in an embodiment;

[0068] FIG. 8 is a schematic diagram of a correlation curve between the actual inductance value of the inductor of the susceptor of the S430 stainless steel measured in an embodiment and the heating temperature of the susceptor;

[0069] Figure 9 is a schematic diagram of control steps of the MCU controller to determine the susceptor temperature based on the phase difference ΔΦ detected by the phase difference detection unit in one embodiment;

[0070] Figure 10 is a schematic diagram of waveforms of the resonant current or resonant voltage in operation of the LC oscillator in one embodiment;

[0071] Figure 11 is a schematic diagram of control steps of the MCU controller in another embodiment;

[0072] Figure 12 is a schematic diagram of control steps of the MCU controller in another embodiment;

[0073] Figure 13 is a schematic diagram of an electronic aerosol provision device in another embodiment. DETAILED DESCRIPTION

[0074] For the purpose of facilitating the understanding of the present application, the present application will be described in more detail below with reference to the accompanying drawings and specific embodiments.

[0075] One embodiment of the present application proposes an electronic aerosol provision device for heating an aerosol generating substrate to generate an aerosol. In some embodiments, the electronic aerosol provision device can comprise two or more parts that are separate from or replaceable with each other, which when combined form a complete combined use state of the electronic aerosol provision device and can generate an aerosol in response to a user's operation.

[0076] In some embodiments, the electronic aerosol provision device can form an aerosol for smoking by heating a solid aerosol generating substrate and volatilizing or releasing at least one component of the solid aerosol generating substrate. In some embodiments, the solid aerosol generating substrate preferably uses a solid substrate, which can include one or more of a powder, a granule, a fragment, a strip, a band, or a sheet of one or more of a vanilla leaf, a dried flower, a volatile flavoring herb, a tobacco leaf, a homogenized tobacco, and an expanded tobacco; or the solid substrate can contain additional tobacco or non-tobacco volatile flavoring compounds to be released when the substrate is heated.

[0077] In one embodiment, the electronic aerosol provision device for heating a solid aerosol generating substrate can be configured as shown in Figure 1, comprising:

[0078] a chamber in which the aerosol generating substrate 1000 is removably received;

[0079] an inductor coil 260 for generating a varying magnetic field under an alternating current;

[0080] The susceptor 30, at least a portion of which extends into the chamber, is configured to be inductively coupled with the inductor coil 260 and to heat up under penetration of a varying magnetic field, thereby heating the aerosol generating substrate 1000, such as a cigarette, to volatilize at least one component of the aerosol generating substrate 1000 to form an aerosol for smoking.

[0081] The electric cell 210 is a rechargeable direct current cell that can output a direct current. The circuit 220 is connected to the rechargeable electric cell 210 by appropriate electrical connections and is configured to convert the direct current output from the electric cell 210 into an alternating current having a suitable frequency and to supply the alternating current to the inductor coil 260.

[0082] In one embodiment, the direct current supply voltage provided by the electric cell 210 is in the range of about 2.5 volts to about 9.0 volts, and the direct current output by the electric cell 210 is in the range of about 2.5 A to about 20 A. In a specific embodiment, the direct current supply voltage provided by the electric cell 210 is in the range of 3.2 volts to 4.2 volts.

[0083] In some embodiments, the circuit 220 is configured to drive an alternating current through the inductor coil 260 at a predetermined frequency, thereby causing the inductor coil 260 to generate a varying magnetic field that penetrates the receiving chamber 270. In some embodiments, the frequency of the alternating current supplied by the circuit 220 to the inductor coil 260 is in the range of 80 KHz to 2000 KHz; more specifically, the frequency can be in the range of about 200 KHz to 800 KHz; more specifically, the frequency can be in the range of about 400 KHz to 800 KHz; more specifically, the frequency can be in the range of about 600 KHz to 1500 KHz.

[0084] In some embodiments, the inductor coil 260 is wound from a low resistivity wire material, such as copper wire, silver wire, or the like. In yet other embodiments, the inductor coil 260 is wound from a litz wire, which has multiple strands or bundles of wire filaments that are more advantageous for carrying an alternating current.

[0085] In some embodiments, the susceptor 30 is an inductive heating element that heats up under penetration of a varying magnetic field. The susceptor 30 is made of a metal or an alloy that is susceptible to induction, such as stainless steel grade 430 (SS430), stainless steel grade 420 (SS420), and an alloy containing iron and nickel, such as permalloy. In the embodiment shown in FIG. 1, the susceptor 30 is configured in the shape of a pin or a blade or a needle that is inserted into a solid aerosol generating substrate for heating. In yet other embodiments, the susceptor 30 is configured in the shape of a tube that at least partially surrounds or bounds the chamber for heating from the outer surface or the outside of a solid aerosol generating substrate.

[0086] In yet other embodiments, the electronic aerosolization device is capable of generating an aerosol by heating a liquid aerosol-generating substrate; in some embodiments, the liquid aerosol-generating substrate includes at least one of propylene glycol, glycerol, and the like. For example, FIG. 13 illustrates a schematic diagram of an electronic aerosolization device in one embodiment, in which the electronic aerosolization device includes an atomizer 100 for atomizing a liquid aerosol-generating substrate to generate an aerosol, and a power supply mechanism 200 for supplying power to the atomizer 100. As shown in FIG. 13, the power supply mechanism 200 includes:

[0087] a proximal end 2110 and a distal end 2120 facing away from each other in a longitudinal direction; in use, the proximal end 2110 is an end for receiving the atomizer 100;

[0088] a receiving cavity 270 disposed adjacent to the proximal end 2110 and along a longitudinal extension of the power supply mechanism 200; and the receiving cavity 270 has an opening facing or located at the proximal end 2110 in the longitudinal direction; in use, the atomizer 100 can be received into or removed from the receiving cavity 270 through the opening;

[0089] a rechargeable battery 210 for outputting electric power; and the battery 210 is disposed proximate to the distal end 2120;

[0090] a charging interface 240 for charging the rechargeable battery 210; and the charging interface 240 is disposed between the battery 210 and the distal end 2120;

[0091] an inductive coil 260 in the form of a substantially solenoid coil disposed around the receiving cavity 270;

[0092] a circuit 220 integrated or disposed on a circuit board, such as a PCB board or a FPC board, for controlling operation of the power supply mechanism 200, in particular, the circuit 220 controls the electric power output by the battery 210.

[0093] According to FIG. 13, the power supply mechanism 200 further includes:

[0094] an airflow sensor 250, such as a microphone / MEMS sensor, for sensing an airflow through the atomizer 100 when a user puffs on the atomizer 100; and the circuit 220 controls the electric power output by the battery 210 based on a sensing result of the airflow sensor 250. In the embodiment shown in FIG. 13, the airflow sensor 250 is disposed between the battery 210 and the receiving cavity 270. In yet other embodiments, the airflow sensor 250 can also be mounted or fastened or integrated on the circuit board on which the circuit 220 is disposed. Or in yet other embodiments, the airflow sensor 250 is supported and fixed within the power supply mechanism 200 by a separate support element, such as a plastic bracket.

[0095] In the embodiment shown in FIG. 13, the power supply mechanism 200 is configured to induce the heater 100 to heat the liquid aerosol generating substrate by generating a varying magnetic field through the receiving cavity 270; specifically, the susceptor 30 can be arranged in the heater 100 and can be penetrated by the varying magnetic field to generate heat when the heater 100 is received in the receiving cavity 270 to heat the liquid aerosol generating substrate to generate an aerosol.

[0096] According to the embodiment shown in FIG. 13, the heater 100 includes:

[0097] a housing 10; a liquid storage cavity 12 formed or defined in the housing 10 for storing the liquid aerosol generating substrate; a susceptor 30 for heating the liquid aerosol generating substrate to generate an aerosol; and a liquid guide element 20 for transferring the liquid aerosol generating substrate between the liquid storage cavity 12 and the susceptor 30; the liquid guide element 20 absorbs the liquid aerosol generating substrate and transfers or provides the liquid aerosol generating substrate to the susceptor 30 to heat the liquid aerosol generating substrate to generate an aerosol.

[0098] According to the embodiment shown in FIG. 13, a partition wall 11 is arranged in the housing 10 and extends in the longitudinal direction of the heater 100. The partition wall 11 and the housing 10 define the liquid storage cavity 12 for storing the liquid aerosol generating substrate. In addition, the partition wall 11 surrounds and defines an aerosol output channel in the housing 10 for outputting the aerosol to the air outlet 111.

[0099] In the embodiment shown in FIG. 13, the liquid guide element 20 is configured to be located in the partition wall 11; and in the embodiment shown in FIG. 13, the liquid guide element 20 is configured to be a longitudinally extending hollow cylinder. In some embodiments, the liquid guide element 20 is made of a capillary material or a porous material, such as a sponge, cotton fibers, or a porous body such as a porous ceramic body, etc. The outer surface of the liquid guide element 20 is configured as a liquid absorbing surface for absorbing the liquid aerosol generating substrate from the liquid storage cavity 12; in some specific embodiments, the partition wall 11 is provided with a plurality of perforations, and the outer surface of the liquid guide element 20 absorbs the liquid aerosol generating substrate in the liquid storage cavity 12 through the perforations. The inner surface of the liquid guide element 20 is configured as an atomizing surface; the susceptor 30 is combined with the inner surface of the liquid guide element 20 and heats at least part of the liquid aerosol generating substrate in the liquid guide element 20 to generate an aerosol.

[0100] In yet other embodiments, the liquid guiding element 20 can also be configured in various regular or irregular shapes and partially in fluid communication with the liquid storage chamber 12 to receive the liquid aerosol generating substrate. Or in other variant embodiments, the liquid guiding element 20 can be more regular or irregular in shape, such as a polygonal block shape, a groove shape with grooves on the surface, or an arch shape with hollow channels inside, etc. Or in yet other variant embodiments, the susceptor 30 can be combined on the liquid guiding element 20 by printing, deposition, sintering or physical assembly, etc. In some other variant embodiments, the liquid guiding element 20 can have a flat or curved surface for supporting the susceptor 30, and the susceptor 30 is formed on the flat or curved surface of the porous liquid guiding element 20 by means of mounting, printing, deposition, etc.

[0101] In the embodiment shown in FIG. 13, the susceptor 30 is an induction heating element that can be heated by a variable magnetic field. The susceptor 30 is made of a metal or alloy with magnetic susceptibility, such as stainless steel grade 430 (SS430), stainless steel grade 420 (SS420), and alloy materials containing iron and nickel, such as permalloy. In some specific embodiments, the susceptor 30 has a length of 2-10 mm; the susceptor 30 has an inner diameter of 1.5-8 mm; and the tube wall thickness of the tubular susceptor 30 is 0.05-0.2 mm. For example, in some specific embodiments, the susceptor 30 has a length of 4-8 mm. As shown in FIG. 13, the susceptor 30 is in a tubular shape closed in the circumferential direction; and the susceptor 30 is in a mesh structure with a plurality of holes to make the susceptor 30 fluid permeable; so that in use, the generated aerosol is released or delivered to the air outlet 111 after passing through the susceptor 30. Or in yet other embodiments, the susceptor 30 can be configured in a solenoid shape, or more shapes such as a sheet shape, a cylinder shape, etc.

[0102] In some embodiments, the inductor coil 260 has an extension length of 6-15 mm; the inductor coil 260 has about 6-12 turns; the length of the susceptor 30 is less than the length of the inductor coil 260; and when the atomizer 100 is received in the receiving chamber 270, the susceptor 30 is substantially completely located in the inductor coil 260.

[0103] FIG. 2 shows a schematic diagram of the circuit 220 in an embodiment, which includes, in the embodiment:

[0104] a capacitor connected with the inductor coil 260 to form an LC oscillator 222; and a bridge 223 connected between the LC oscillator 222 and the battery 210 to drive the LC oscillator 222 to oscillate, thereby forming an alternating current flowing through the inductor coil 260.

[0105] In some embodiments, the LC oscillator 222 can be a series LC oscillator formed by the inductor 260 in series with at least one capacitor; or, the LC oscillator 222 can be a parallel LC oscillator formed by the inductor 260 in parallel with at least one capacitor. Or in more embodiments, the LC oscillator 222 is an LC oscillator formed by the inductor 260 connected with at least two capacitors, such as the commonly used symmetric half-bridge LC oscillator also known as LCC oscillator, etc.

[0106] Figure 3 shows a schematic diagram of the basic components of the circuit 220 of one specific embodiment, in which the LC oscillator 222 is a symmetric half-bridge LC oscillator with two symmetric bridge arms; specifically, in Figure 3, the LC oscillator 222 includes:

[0107] a series capacitor CI and a capacitor C2; wherein the first end of the capacitor CI is connected to the positive pole of the battery 210, and the second end is connected to the first end of the capacitor C2; the second end of the capacitor C2 is connected to the negative pole of the battery 210 through the ground; the second end of the capacitor CI and the first end of the capacitor C2 are simultaneously connected to the second end of the inductor 260. Or in embodiments, the capacitor CI and / or the capacitor C2 can each include a plurality of capacitors in parallel. Using a plurality of capacitors in parallel to provide the capacitance of the capacitor CI and / or the capacitor C2 can relatively reduce the capacitance requirement of each capacitor.

[0108] In the embodiment shown in Figure 3, the bridge 223 is a half-bridge matched to the symmetric half-bridge LC oscillator; specifically in Figure 3, the bridge 223 (e.g. half-bridge) includes a series of switch tube Ql and switch tube Q2; in the connection of Figure 3, the first end of the switch tube Ql is connected to the positive pole of the battery 210, and the second end is connected to the first end of the inductor 260; the first end of the switch tube Q2 is connected to the first end of the inductor 260, and the second end is connected to the negative pole of the battery 210 through the ground. And, the conduction and disconnection of the switch tube Ql and the switch tube Q2 are controlled by the PWM control signal issued by the switch tube drive 225. The PWM control signal issued by the switch tube drive 225 is generated by the MCU controller 224. Or in some other common variant embodiments, the bridge 223 can also use a full-bridge or H-bridge including four switch tubes. In the embodiment of Figure 3, the MCU controller 224 drives the LC oscillator 222 to oscillate by controlling the alternating conduction and disconnection of the switch tube Ql and the switch tube Q2, thereby forming an alternating current flowing through the inductor 260, causing the inductor 260 to generate a varying magnetic field to induce the susceptor 30 to heat and generate aerosol. Or in some other embodiments, the LC oscillator 222 can also be an asymmetric half-bridge LC oscillator 222 including only the capacitor C2 in series with the inductor 260, having only one oscillation bridge arm composed of the capacitor C2 and the inductor 260 in series.

[0109] In some embodiments, the MCU controller 224 controls the switch tube drive 225 to modulate the PWM control signal to make the switch tube Q1 and the switch tube Q2 alternately turn on and off, so as to drive the LC oscillator 222 to oscillate to make the inductor coil 260 generate a changing magnetic field. In some embodiments, the MCU controller 224 controls the power provided to the susceptor 30 to make the susceptor 30 heat according to a predetermined heating curve. In a specific control, the MCU controller 224 controls the inductor coil 260 to provide power to the susceptor 30 through the magnetic field to make the susceptor 30 heat the aerosol generating substrate according to the predetermined heating curve by controlling the duty cycle and / or the frequency of the PWM control signal, etc.

[0110] According to the embodiments shown in FIG. 2 and FIG. 3, the circuit 220 further comprises:

[0111] a phase difference detection unit 221 for detecting the phase difference ΔΦ between the resonant voltage in the operation of the LC oscillator 222 and the PWM control signal.

[0112] In some embodiments, the MCU controller 224 can find the actual inductance value Ls of the inductor coil 260 in operation during the heating process through the phase difference ΔΦ detected by the phase difference detection unit 221, and further determine the temperature of the susceptor 30. Specifically, the control step of the MCU controller 224 to determine the temperature of the susceptor 30 according to the phase difference ΔΦ detected by the phase difference detection unit 221 can refer to the control step shown in FIG. 9; the control step comprises:

[0113] S10, controlling the switch tube drive 225 to modulate the PWM control signal generated according to a given reference frequency to make the switch tube Q1 and the switch tube Q2 alternately turn on and off, so as to drive the LC oscillator 222 to oscillate to make the inductor coil 260 generate a changing magnetic field to induce the susceptor 30 to heat.

[0114] S20, obtaining the phase difference ΔΦ between the resonant voltage in the operation of the LC oscillator 222 and the PWM control signal detected by the phase difference detection unit 221, and controlling the switch tube drive 225 to adjust the frequency of the PWM control signal according to the phase difference ΔΦ, until the phase difference ΔΦ between the resonant voltage in the operation of the LC oscillator 222 and the PWM control signal detected by the phase difference detection unit 221 remains at a predetermined threshold value, to determine the optimal resonant frequency fr of the LC oscillator 222 of the susceptor 30 when heating.

[0115] The meaning that the phase difference ΔΦ of the above resonance voltage and the PWM control signal is kept at a predetermined threshold is that the phase difference ΔΦ of the two can be limited to float within a smaller interval around the predetermined threshold. In some examples, the predetermined threshold can be zero or close to zero, for example, when the LC oscillator 222 is in a determined optimal resonance frequency fr working state, the above phase difference ΔΦ is positive, which should be kept less than the predetermined threshold. For example, in some embodiments, the phase difference ΔΦ of the predetermined threshold close to zero can be set to a phase difference ΔΦ less than π / 20; or smaller, for example, less than π / 30.

[0116] S30, according to the determined optimal resonance frequency fr of the LC oscillator 222, the actual inductance value Ls of the inductor coil 260 in operation is calculated or determined by table lookup, etc.; and then the temperature of the susceptor 30 is calculated or determined by table lookup, etc. according to the actual inductance value Ls of the inductor coil 260 in operation.

[0117] Wherein, the optimal resonance frequency is a term in the field of electricity or physics, or can also be called the natural resonance frequency, which refers to the specific frequency of the LC oscillator determined by its own structure and parameters without external excitation; When working at this frequency, the LC oscillator will resonate, that is, the vibration amplitude will increase sharply; Usually the efficiency of the LC oscillation system is the largest when working at this frequency.

[0118] In some specific embodiments, the reference frequency given in step S10 is the optimal resonance frequency fr of the LC oscillator 222 when the susceptor 30 is not started heating (room temperature). When starting heating, the MCU controller 224 controls the LC oscillator 222 to oscillate and start heating according to the optimal resonance frequency fr of the LC oscillator 222 at room temperature as the reference frequency.

[0119] In some specific embodiments, the reference frequency given in step S10 is set by the technician according to the change range of the optimal resonance frequency fr in the heating temperature range, combined with the experience value of a large number of tests. For example, in some optional embodiments, within the heating temperature range of the susceptor 30, the optimal resonance frequency fr of the LC oscillator 222 can be approximately between 400KHz and 800KHz; Then the given reference frequency can be set to 400KHz to 600KHz combined with the experience of the technician.

[0120] In step S30, the temperature of the susceptor 30 is determined based on the actual inductance value Ls of the inductor coil 260 in operation, by calculation or table lookup, etc. The actual inductance value Ls of the inductor coil 260 in operation has a monotonic relationship with the temperature of the susceptor 30. Specifically, the inductor coil 260 with the susceptor 30 coupled inside in operation is equivalent to a core inductance (physics terminology); the actual inductance value Ls of the inductor coil 260 can be obtained according to the formula: Ls = Lc + Lr; in the formula, Lc is the inductance value of the inductor coil 260 itself, and Lr is the equivalent inductance value of the susceptor 30 acting as a core in operation. In operation, for a given inductance value Lc of the inductor coil 260 itself, the equivalent inductance value Lr of the susceptor 30 varies with the temperature of the susceptor 30; further, the actual inductance value Ls of the inductor coil 260 has a monotonic relationship with the temperature of the susceptor 30, so that the temperature of the susceptor 30 can be determined based on the actual inductance value Ls of the inductor coil 260 in operation by calculation or table lookup, etc.

[0121] For example, Figure 5 shows a curve of the actual inductance value Ls of the inductor coil 260 inductively coupled with the susceptor 30 of permalloy with a brand of 1J85 in operation and the temperature of the susceptor 30 in an embodiment. As can be seen from Figure 5, in the temperature range from room temperature to about 280°C, the actual inductance value Ls of the inductor coil 260 in operation is substantially monotonically increasing with the temperature of the susceptor 30; therefore, for a use range generally below 280°C, it is advantageous to determine the heating temperature of the susceptor 30 by obtaining the actual inductance value Ls of the inductor coil 260 and then looking up a table or fitting calculation, etc.

[0122] For example, Figure 8 shows a curve of the actual inductance value Ls of the inductor coil 260 inductively coupled with the susceptor 30 of stainless steel with a brand of S430 in operation and the temperature of the susceptor 30 in an embodiment. As can be seen from Figure 8, in the temperature range from room temperature to about 350°C, the actual inductance value Ls of the inductor coil 260 in operation is substantially monotonically increasing with the temperature of the susceptor 30; therefore, for a use range generally below 280°C, it is advantageous to determine the heating temperature of the susceptor 30 by obtaining the actual inductance value Ls of the inductor coil 260 and then looking up a table or fitting calculation, etc.

[0123] In step S30, the actual inductance value Ls of the inductor coil 260 in operation is determined based on the optimal resonant frequency fr of the LC oscillator 222, by calculation or table lookup, etc. The optimal resonant frequency fr of the LC oscillator 222 has a relationship with the actual inductance value Ls of the inductor coil 260 in operation; specifically, their relationship can follow the following physical formula:

[0124] In the formula, C is the total capacitance value of the LC oscillator 222. In a specific embodiment, for an LC oscillator 222 with a given electronic device, the capacitance value C is defined by the capacitor CI and the capacitor C2 and is constant in operation, so that the optimal resonant frequency fr has a unique correlation with the actual inductance value Ls of the inductor coil 260, i.e. the actual inductance value Ls of the inductor coil 260 can be calculated or looked up from a table, etc. by the optimal resonant frequency fr. In heating, the optimal resonant frequency fr of the LC oscillator 222 changes with the temperature of the susceptor 30. Then in step S20, the optimal resonant frequency fr of the LC oscillator 222 in heating is found or determined by measuring the phase difference AF of the resonant voltage of the LC oscillator 222 in operation and the PWM control signal.

[0125] In some embodiments, step S20 determines the optimal resonant frequency fr of the LC oscillator 222 in heating by sweeping the frequency of the PWM control signal. Specifically: when the frequency of the PWM control signal driving the LC oscillator 222 to oscillate is the same as the optimal resonant frequency fr of the LC oscillator 222, the LC oscillator 222 can reach a complete resonance state; when the LC oscillator 222 operates in the complete resonance state, the phase of the resonant voltage of the LC oscillator 222 is the same as that of the PWM control signal, e.g. as shown in FIG. 6, the start and end time of the high level of the PWM control signal Vp is exactly the positive and negative maximum points of the resonant voltage Vr of the LC oscillator 222, and their phase difference AF is zero. When the frequency of the PWM control signal driving the LC oscillator 222 to oscillate is different from the optimal resonant frequency fr of the LC oscillator 222, the LC oscillator 222 cannot reach a complete resonance state; when the LC oscillator 222 operates in an incomplete resonance state, the phase of the resonant voltage of the LC oscillator 222 is different from that of the PWM control signal, e.g. as shown in FIG. 7, the start and end time of the high level of the PWM control signal Vp deviates from the positive and negative maximum points of the resonant voltage Vr of the LC oscillator 222, and their phase difference AF is not zero; and the greater the deviation of the frequency of the PWM control signal from the optimal resonant frequency fr of the LC oscillator 222, the greater the phase difference AF. In step S20, the frequency of the PWM control signal is adjusted in a manner similar to sweeping, and the optimal resonant frequency fr of the LC oscillator 222 in heating is determined by detecting when the phase difference AF is zero.

[0126] In some specific embodiments, the manner of adjusting the frequency of the PWM control signal in step S20 can be to gradually increase or decrease the frequency of the PWM control signal based on the given reference frequency in step S10, and sweep until the optimal resonant frequency fr of the LC oscillator 222 is found.

[0127] In some specific embodiments, the circuit can further comprise a frequency synthesizer chip arranged between the MCU controller 224 and the switch tube driver 225; the frequency synthesizer chip is a chip for providing or outputting a high-precision, high-stability frequency signal, and has a smaller frequency adjustment precision. In embodiments, the MCU controller 224 controls the frequency synthesizer chip to output a varying frequency, so that the switch tube driver 225 adjusts the generated PWM control signal; a general frequency synthesizer chip can meet a frequency range of 1 kHz-4.4 GHz, and the frequency adjustment precision can reach a minimum step of 1 Hz. Specifically, in step S20, the MCU controller 224 controls the frequency synthesizer chip to adjust the frequency of the PWM control signal in a manner of increasing or decreasing the minimum step value each time to sweep the frequency.

[0128] In some specific embodiments, the manner of adjusting the frequency of the PWM control signal in step S20 can be that the MCU controller 224 increases the frequency of the PWM control signal in a forward step-by-step manner by the minimum step value each time; that is, the MCU controller 224 adjusts the frequency of the PWM control signal = reference frequency (for example, 400 KHz) + n x minimum step value (1 KHz); where n is a positive integer. Or in yet some embodiments, the manner of adjusting the frequency of the PWM control signal in step S20 can be that the MCU controller 224 decreases the frequency of the PWM control signal in a reverse step-by-step manner by the minimum step value each time.

[0129] Or as shown in FIG. 9, the phase difference ΔΦ of the resonant voltage of the LC oscillator 222 and the PWM control signal has a correlation with the degree of deviation of the optimal resonant frequency fr guided by the temperature change; then in step S20, the MCU controller 224 can also be configured to: directly determine the optimal resonant frequency fr of the current LC oscillator 222 by calculation or table lookup, etc. according to the phase difference ΔΦ of the resonant voltage of the LC oscillator 222 and the PWM control signal. In the above embodiments, the optimal resonant frequency fr of the current LC oscillator 222 is determined by the phase difference ΔΦ, and further the temperature of the susceptor 30 is determined; this can reduce the voltage stabilizing source device required by the circuit in determining the temperature by the apparent ohmic resistance, which is advantageous for reducing the circuit devices.

[0130] In some embodiments, FIG. 4 shows a basic device schematic diagram of the phase difference detection module 221 applicable to a signal frequency greater than 500 KHz in an embodiment; according to FIG. 4, the phase difference detection module 221 of this embodiment comprises:

[0131] The waveform converter 2211a is used to convert the resonant voltage of the sinusoidal waveform of the LC oscillator 222 into a square wave signal; the resonant voltage of the sinusoidal waveform which is difficult to identify the phase is converted into the shape of a square wave by the waveform converter 2211a, and then it is easy to sample and identify. The square wave signal which is converted by the waveform converter 2211a is the same as the resonant voltage of the sinusoidal waveform in period, direction and phase, and then the square wave signal which is easy to identify is sampled and detected. Of course, the voltage amplitude of the converted square wave signal is lower than the amplitude of the resonant voltage signal of the sinusoidal waveform, so that the signal strength is suitable for the signal interface of the downstream to receive.

[0132] According to FIG. 4, the phase difference detection module 221 further includes:

[0133] The direction comparator 2212a is used to compare the direction of the square wave signal converted by the waveform converter 2211a and the PWM control signal; and the phase comparator chip 2213a is used to calculate the phase difference ΔΦ of the square wave signal converted by the waveform converter 2211a and the PWM control signal by comparison.

[0134] In yet another embodiment, FIG. 3 shows a basic device schematic diagram of the phase difference detection module 221 suitable for a frequency less than 500 KHz according to another embodiment, according to the diagram shown in FIG. 3, the hardware of the phase difference detection module 221 includes:

[0135] The series-connected voltage dividing resistor R1 and voltage dividing resistor R2; the resonant voltage of the sinusoidal waveform of the LC oscillator 222 is divided by the voltage dividing resistor R1 and voltage dividing resistor R2, and then output synchronously to facilitate subsequent sampling and identification; the voltage stabilizing tube Z prevents the voltage of the synchronous output after voltage division from being too large, and provides protection for the subsequent circuit; the high-speed comparator or zero-crossing comparator U1 is used to obtain the time when the resonant voltage of the LC oscillator 222 is zero by comparison operation, and then output a square wave signal representing the time when the resonant voltage of the LC oscillator 222 is zero; or, the high-speed comparator or zero-crossing comparator U1 is used to convert the resonant voltage of the LC oscillator 222 into a pulse square wave signal after comparison operation, and the frequency, period and phase of the pulse square wave signal are the same as those of the resonant voltage of the LC oscillator 222; for example, in the calculation, the high-speed comparator or zero-crossing comparator U1 compares the resonant voltage of the LC oscillator 222 with zero, and outputs high level if it is greater than zero, and outputs low level if it is less than zero;

[0136] A TDC (Time-to-Digital Converter) chip 226 is configured to compare the PWM control signal with the pulse square wave signal outputted by the high-speed comparator or zero-crossing comparator U1, i.e. to calculate the time difference of the pulses. In some embodiments, the TDC (Time-to-Digital Converter) chip 226 is a commonly used electronic device that can measure the time difference between one pulse or two different pulses, with an error of only tens of ps. The MCU controller 224 calculates the phase difference ΔΦ result according to the time difference calculated by the TDC (Time-to-Digital Converter) chip 226 and the period of the signal; or the time difference calculated by the TDC (Time-to-Digital Converter) chip 226 is equivalent to the phase difference ΔΦ.

[0137] In some embodiments, since the LC oscillator 222 of the above symmetric half-bridge has a symmetric oscillation bridge arm configuration, the duty cycle of the PWM control signal is basically constant at 50%, and the MCU controller 224 controls the PWM control signal with a 50% duty cycle to drive the switch tube Q1 and the switch tube Q2 to alternately turn on or off. During oscillation, the resonant current or resonant voltage of the LC oscillator 222 in operation is a symmetric sine or cosine resonant change curve, as shown in FIG. 10. In operation, the intensity of the resonant voltage and the resonant current are related, and referring to FIG. 10, the resonant voltage is about 1 / 4 period ahead of the resonant current. In some alternative embodiments, the MCU controller 224 determines the temperature of the susceptor 30 according to the phase difference between the resonant current of the LC oscillator 222 and the PWM control signal.

[0138] In some embodiments, the MCU controller 224 is further configured to control to stop or interrupt the generation of the PWM control signal when it is determined that the temperature of the susceptor 30 exceeds a predetermined threshold, so as to prevent the LC oscillator 222 from oscillating and thus prevent the inductor coil 260 from continuing to generate a magnetic field, which is advantageous for preventing the susceptor 30 from burning or overheating. Alternatively, in some other embodiments, the MCU controller 224 is further configured to determine the user's puffing action according to the phase difference ΔΦ between the resonant voltage of the LC oscillator 222 and the PWM control signal. Specifically, the temperature of the susceptor 30 is determined according to the optimal resonant frequency fr of the LC oscillator 222 determined according to the phase difference ΔΦ, and then the temperature of the susceptor 30 is calculated or looked up according to the determined optimal resonant frequency fr of the LC oscillator 222; and when it is determined that the temperature of the susceptor 30 decreases, it indicates that the user's puffing action causes air to flow through the susceptor 30 to reduce the temperature of the susceptor 30, thereby determining the user's puffing action.

[0139] In yet other embodiments, based on the correlation between the phase difference ΔΦ of the resonant voltage of the LC oscillator 222 and the PWM control signal at a given frequency and the susceptor 30 during heating, FIG. 11 shows a schematic diagram of the control steps of the MCU controller 224 of yet another embodiment, including:

[0140] S10a, the switch tube driver 225 is controlled to drive the switch tube Q1 and the switch tube Q2 to alternately turn on or off at a given frequency, so as to drive the LC oscillator 222 to oscillate to make the inductor coil 260 generate a magnetic field to induce the susceptor 30 to heat.

[0141] S20a, the phase difference ΔΦ of the resonant voltage of the LC oscillator 222 and the PWM control signal detected by the phase difference detection unit 221 is obtained.

[0142] According to FIG. 11, in some embodiments, the control steps of the MCU controller 224 further include: S30a, adjusting the frequency of the PWM control signal so that the phase difference ΔΦ of the resonant voltage of the LC oscillator 222 and the PWM control signal remains zero, so that the LC oscillator 222 is basically kept in the maximum resonance state.

[0143] For example, in some embodiments, when the phase difference ΔΦ of the resonant voltage of the LC oscillator 222 and the PWM control signal is greater than zero or positive, it indicates that the optimal resonant frequency fr of the LC oscillator 222 is reduced due to the temperature rise of the susceptor 30, and at this time, if it is required to keep the LC oscillator 222 in the maximum resonance state, the frequency of the PWM control signal needs to be reduced. For another example, in some exemplary embodiments, the controller can also determine the puffing action of the user according to the change of the phase difference ΔΦ of the resonant voltage or the resonant current of the LC oscillator and the PWM control signal. For example, in use, when the phase of the resonant voltage of the LC oscillator 222 and the PWM control signal deviates, i.e., the phase difference ΔΦ changes from zero or close to zero to less than zero or negative, it may indicate that the temperature of the susceptor 30 is reduced due to the air flowing through the susceptor 30 by the user's puffing action, thereby causing the optimal resonant frequency fr of the LC oscillator 222 to rise, and at this time, if it is required to keep the LC oscillator 222 in the maximum resonance state, the frequency of the PWM control signal needs to be increased.

[0144] Or in yet some embodiments, the frequency of the PWM control signal is adjusted by keeping the phase difference ΔΦ between the resonant voltage of the LC oscillator 222 and the PWM control signal at zero, so as to keep the frequency of the PWM control signal substantially the same or close to the optimal resonant frequency fr of the LC oscillator 222. Or in an embodiment shown in FIG. 12, the MCU controller 224 controls the calibration or update of the reference frequency for starting the LC oscillator 222 to work, and the control steps for the calibration or update of the reference frequency include:

[0145] S100, the switch tube drive 225 modulates the PWM control signal according to the predetermined reference frequency, so as to drive the switch tube Q1 and the switch tube Q2 to alternately turn on and off, thereby driving the LC oscillator 222 to oscillate.

[0146] S200, the phase difference ΔΦ between the resonant voltage of the LC oscillator 222 in operation and the PWM control signal detected by the phase difference detection unit 221 is obtained, and the frequency of the PWM control signal is adjusted by the switch tube drive 225 according to the phase difference ΔΦ.

[0147] S300, the frequency of the PWM control signal when the phase difference ΔΦ detected by the phase difference detection unit 221 is zero is obtained, and the frequency of the PWM control signal when the phase difference ΔΦ is zero is stored as the calibrated or updated reference frequency.

[0148] Then when the electronic atomization device starts heating, the MCU controller 224 controls the generation of the PWM control signal according to the calibrated or updated reference frequency, and drives the LC oscillator 222 to start working so as to start the heating of the susceptor 30.

[0149] In some embodiments, the above calibration or update steps can be performed after the production and assembly of the electronic atomization device are completed, such as after the factory or before the sale. Or in yet some embodiments, the above calibration or update steps can be performed according to a predetermined frequency, such as every 1 month, 2 months or 6 months. For the user in use, it is advantageous to calibrate or update the reference frequency for starting the heating of the device.

[0150] The above description is only an embodiment of the present application, and does not limit the patent scope of the present application, and any equivalent structure or equivalent process transformation using the content of the specification and drawings, or direct or indirect application in other related technical fields, are also included in the patent protection scope of the present application.

[0151] Finally, it should be noted that: the above examples are only used to illustrate the technical solutions of the present application, but not to limit them; under the idea of the present application, the technical features in the above examples or different embodiments can also be combined, the steps can be implemented in any order, and there are many other changes of different aspects of the present application as described above, which are not provided in details for simplicity; although the present application has been described in detail with reference to the foregoing examples, those skilled in the art should understand that: it can still modify the technical solutions recorded in the foregoing examples, or make equivalent replacement for part of the technical features; and these modifications or replacements do not make the essence of the corresponding technical solutions deviate from the scope of the technical solutions of the embodiments of the present application.

Claims

1. An electronic atomizing device, characterized in that, include: Receptors are used to heat the aerosol-generating matrix to produce aerosols; An LC oscillator, comprising an inductor and a capacitor, is configured to guide alternating current through the inductor, thereby driving the inductor to provide energy to the sensor, causing the sensor to heat the aerosol to generate a matrix; The controller is configured as follows: The LC oscillator is driven by a PWM control signal to generate an alternating current flowing through the inductor coil, and the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is detected. The frequency of the PWM control signal is adjusted so that the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is maintained at a predetermined threshold.

2. The electronic atomizing device as described in claim 1, characterized in that, The controller is also configured to adjust the frequency of the PWM control signal so that the phase difference between the resonant voltage of the LC oscillator and the PWM control signal is kept at or close to zero.

3. The electronic atomizing device as described in claim 1 or 2, characterized in that, The controller is also configured to: The optimal resonant frequency of the LC oscillator is determined based on the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal being a predetermined threshold. The temperature of the sensor is determined based on the optimal resonant frequency of the LC oscillator.

4. The electronic atomizing device as described in claim 3, characterized in that, Determining the temperature of the sensor based on the optimal resonant frequency of the LC oscillator includes: The actual inductance value of the inductor coil during operation is determined based on the optimal resonant frequency of the LC oscillator, and the temperature of the sensor is then determined by looking up a table or by calculation based on the actual inductance value.

5. The electronic atomizing device as described in claim 1 or 2, characterized in that, The controller is also configured to: The optimal resonant frequency of the LC oscillator is determined based on the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal being a predetermined threshold. The frequency of the PWM control signal is adjusted so that it is the same as or close to the optimal resonant frequency of the LC oscillator.

6. The electronic atomizing device as described in claim 1 or 2, characterized in that, Also includes: A phase difference detection module is used to detect the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal; The phase difference detection module includes: A waveform converter is used to convert the resonant voltage or resonant current of the LC oscillator into a square wave signal, wherein the square wave signal has the same frequency and phase as the resonant voltage or resonant current of the LC oscillator. The phase difference detection module detects the phase difference by comparing the square wave signal and the PWM control signal.

7. The electronic atomizing device as described in claim 6, characterized in that, The waveform converter includes a high-speed comparator or a zero-crossing comparator.

8. The electronic atomizing device as described in claim 6, characterized in that, The phase difference detection module further includes: A time-to-digital converter chip is used to calculate the time difference between the square wave signal and the PWM control signal, and the controller obtains the phase difference based on the time difference; Alternatively, a phase comparator chip can be used to compare and calculate the phase difference between the square wave signal and the PWM control signal, thereby obtaining the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal.

9. The electronic atomizing device as described in claim 1 or 2, characterized in that, The controller is also configured to prevent or interrupt the flow of alternating current guided by the LC oscillator through the inductor coil when it is determined that the temperature of the sensor exceeds a predetermined threshold.

10. The electronic atomizing device as described in claim 1 or 2, characterized in that, The controller is also configured to determine the user's suction action based on the change in the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal.

11. An electronic atomizing device, characterized in that, include: Receptors are used to heat the aerosol-generating matrix to produce aerosols; An LC oscillator, comprising an inductor and a capacitor, is configured to guide alternating current through the inductor, thereby driving the inductor to provide energy to the sensor, causing the sensor to heat the aerosol to generate a matrix; The controller is configured as follows: The LC oscillator is driven by a PWM control signal to generate an alternating current flowing through the inductor coil, and the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is detected. The optimal resonant frequency of the LC oscillator is determined based on the change in the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal, and then the temperature of the sensor is determined based on the optimal resonant frequency of the LC oscillator.

12. The electronic atomizing device as described in claim 11, characterized in that, Determining the temperature of the sensor based on the optimal resonant frequency of the LC oscillator includes: The actual inductance value of the inductor coil during operation is determined based on the optimal resonant frequency of the LC oscillator, and the temperature of the sensor is then determined by looking up a table or by calculation based on the actual inductance value.

13. An electronic atomizing device, characterized in that, include: Receptors are used to heat the aerosol-generating matrix to produce aerosols; An LC oscillator, comprising an inductor and a capacitor, is configured to guide alternating current through the inductor, thereby driving the inductor to provide energy to the sensor, causing the sensor to heat the aerosol to generate a matrix; The controller is configured as follows: The LC oscillator is driven by a PWM control signal with a given reference frequency to generate an alternating current flowing through the inductor coil, and the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is detected. The frequency of the PWM control signal is adjusted, and the reference frequency is updated with the current frequency of the PWM control signal when the phase difference is a predetermined threshold. The LC oscillator is controlled to start working according to the updated reference frequency, so that the sensor starts heating.

14. A control method for an electronic atomizing device, the electronic atomizing device comprising: Receptors are used to heat the aerosol-generating matrix to produce aerosols; An LC oscillator, comprising an inductor and a capacitor, is configured to guide alternating current through the inductor, thereby driving the inductor to provide energy to the sensor, causing the sensor to heat the aerosol to generate a matrix; The method is characterized by comprising: The LC oscillator is driven by a PWM control signal to generate an alternating current flowing through the inductor coil, and the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is detected. The frequency of the PWM control signal is adjusted so that the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is maintained at a predetermined threshold.

15. A control method for an electronic atomizing device, the electronic atomizing device comprising: Receptors are used to heat the aerosol-generating matrix to produce aerosols; An LC oscillator, comprising an inductor and a capacitor, is configured to guide alternating current through the inductor, thereby driving the inductor to provide energy to the sensor, causing the sensor to heat the aerosol to generate a matrix; The method is characterized by comprising: The LC oscillator is driven by a PWM control signal to generate an alternating current flowing through the inductor coil, and the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal is detected. The optimal resonant frequency of the LC oscillator is determined based on the change in the phase difference between the resonant voltage or resonant current of the LC oscillator and the PWM control signal, and then the temperature of the sensor is determined based on the optimal resonant frequency of the LC oscillator.

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