A high-power analog battery

Abstract

The present application relates to the technical field of analog battery, in order to solve the technical problem of the existing analog battery size and mass is too big, the present application discloses a kind of high-power analog battery, including power output unit, it further includes output synchronous following unit, power output unit includes power output circuit, the power input end of power output circuit is connected with the power output end of output synchronous following unit, power output circuit is equipped with discharge power regulating tube, output synchronous following unit is according to the pressure difference signal between the input end and output end of discharge power regulating tube and carries out dynamic adjustment output.Make that output synchronous following unit follows the pressure difference of regulating tube in power output unit and is adjusted or fixed voltage work, always maintain at fixed voltage, reduce the power consumption of power regulating tube itself, reduce the heat release, improve the stability of high-power analog battery system work, meet the test demand of current battery capacity increase.

Description

Technical Field

[0001] This invention relates to the field of simulated battery technology, and more particularly to a high-power simulated battery. Background Technology

[0002] As smartphones become increasingly sophisticated, their battery capacities grow steadily. The widespread adoption of fast charging provides a convenient way to charge these ever-increasing battery capacities. Furthermore, the scale of energy storage installations continues to expand, particularly with the increasing proportion of new energy storage technologies, leading to a greater demand for battery capacity. While this growing battery capacity facilitates the use of various electronic products, it also presents significant challenges to product development and production line testing.

[0003] As the power of the simulated battery increases, so does its power consumption. Furthermore, the output of the simulated battery is unstable and cannot operate stably at a fixed voltage. This limits the power of existing simulated batteries, causing the current and power to fail to meet testing requirements and thus the demands of increasing battery capacity. In addition, the increased power of the simulated battery is accompanied by an increase in size and weight, making it less portable. Summary of the Invention

[0004] The purpose of this invention is to provide a high-power simulated battery to solve the technical problem that existing simulated batteries cannot meet the testing requirements of large-capacity batteries.

[0005] To achieve the above objectives, the specific technical solution of a high-power simulated battery of the present invention is as follows:

[0006] A high-power analog battery includes a power output unit for outputting a final DC power and an output synchronous follower unit for outputting a third DC power. The power output unit includes a power output circuit, the power input terminal of which is connected to the power output terminal of the output synchronous follower unit. The power output circuit is equipped with a discharge power adjustment transistor. The output synchronous follower unit dynamically adjusts the output of the third DC power based on the voltage difference signal between the input and output terminals of the discharge power adjustment transistor. This ensures that when the output synchronous follower unit adjusts or operates at a fixed voltage following the voltage difference of the adjustment transistor in the power output unit, it always maintains a fixed voltage, reducing the power consumption of the power adjustment transistor itself, lowering heat generation, and improving the stability of the high-power analog battery system, thus meeting the testing requirements for increased battery capacity. The reduced heat generation further reduces the size and weight of the high-power analog battery itself, making it lighter and more portable.

[0007] Furthermore, an optocoupler control circuit for feedback differential voltage signals is provided between the power output unit and the output synchronization follower unit. Electrical isolation is achieved through the optocoupler, preventing mutual interference between the two units.

[0008] Furthermore, the output synchronization follower unit includes an LCC circuit for power conversion, a resonant controller for providing a voltage drive signal to the LCC circuit, an optocoupler control circuit that feeds back a differential voltage signal to the resonant controller, and the LCC circuit outputting a third DC power to the power output unit. The LCC circuit is an adjustable switching power supply, which, compared to a linear power supply, can further reduce the size and weight of high-power instruments.

[0009] Furthermore, the output synchronization follower unit also includes a voltage and current feedback circuit for feeding back the parameters of the third DC current to the resonant controller.

[0010] Furthermore, the LCC circuit includes a transformer, a synchronous rectifier controller, and switching transistors Q13 and Q14 controlled by the synchronous rectifier controller. The primary side of the transformer is used for input voltage drive signals, and the secondary side of the transformer is provided with a center tap for outputting a third DC power. The two ends of the secondary side are respectively connected to the first switching terminals of switching transistors Q13 and Q14, the second switching terminals of switching transistors Q13 and Q14 are respectively connected to the synchronous rectifier controller, and the controlled terminals of switching transistors Q13 and Q14 are respectively connected to the synchronous rectifier controller.

[0011] Furthermore, the LCC circuit also includes a primary-side current sampling circuit for feeding back the primary-side current to the resonant controller.

[0012] Furthermore, the discharge power regulating transistor includes a switching transistor Q15 and a switching transistor Q16 controlled by Q15. The controlled terminal of switching transistor Q16 is connected to the output terminal of comparator U6. The non-inverting input terminal of comparator U6 is connected to the second switching terminal of switching transistor Q15. The inverting input terminal of comparator U6 is provided with a reference voltage. A third DC current is input to the first switching terminals of switching transistors Q15 and Q16, and the second switching terminals of switching transistors Q15 and Q16 are used to output the final DC current. The discharge power regulating transistor is a linearly regulated power transistor. During discharge, switching transistor Q15 turns on first, followed by switching transistor Q16. This time delay avoids the current surge caused by simultaneous conduction. Switches Q15 and Q16 are linearly regulated power transistors, improving the output voltage quality.

[0013] Furthermore, the power output unit also includes a charging power adjustment tube used for load testing, and a current sensing resistor, a current range switching switch and an output protection switch are connected in series on the output line of the power output circuit.

[0014] Furthermore, it also includes a voltage adjustment circuit, which is used to obtain a third DC power from the power output unit and feed it back to the output synchronization follower unit through comparator U10 and optocoupler Q33.

[0015] Furthermore, it includes a power factor correction unit for providing a first DC voltage to the output synchronous follower unit. The power factor correction unit has a PFC module, which includes a first common-mode inductor for connection to the mains power, a second common-mode inductor connected to the first common-mode inductor, and a rectifier module connected to the second common-mode inductor. The positive terminal of the rectifier module is connected to the input terminal of coil L1A. The output terminal of coil L1A is connected to the first switching terminal of switch transistor Q1. The second switching terminal of switch transistor Q1 is grounded. The controlled terminal of switch transistor Q1 is connected to the driving terminal of the power factor controller. The output terminal of coil L1A is grounded through capacitor C1. Switch transistor Q1, coil L1A, capacitor C1, and power factor controller constitute a power factor correction circuit. A thermistor is connected in series in the AC circuit of the rectifier module. A relay is connected in parallel to the thermistor. A switch transistor Q2 is also provided for controlling the opening and closing of the relay. Switch transistor Q2 is connected to a first voltage feedback circuit for controlling its conduction and cutoff. The first voltage feedback circuit is used to sample the first DC voltage. Improving the power factor reduces reactive current and enhances power supply efficiency.

[0016] The high-power simulated battery provided by this invention has the following advantages:

[0017] The output voltage drive signal waveform of the resonant controller of the output synchronous follower unit is fed to the LCC circuit for power conversion. After conversion by the LCC circuit, it provides voltage for the output. The voltage and current signals at the output terminal are fed to the voltage and current feedback circuit. The voltage and current feedback signals are transmitted to the feedback terminal of the resonant controller through the optocoupler control circuit, thereby controlling the voltage and current output of the power supply. The output voltage signal of the power output unit is input to the optocoupler control circuit to control the voltage of the output synchronous follower unit to follow the output voltage of the entire high-power analog battery. The pre-stage power supply uses an adjustable LCC switching power supply, which can greatly reduce the size and weight of high-power instruments. The adjustable voltage range of the analog battery output can be increased by voltage follower adjustment. The analog battery power output uses a linearly adjustable power transistor to improve the output voltage quality. Attached Figure Description

[0018] Figure 1 A block diagram of a high-power analog battery system provided by the present invention;

[0019] Figure 2 Functional block diagram of the power factor correction unit provided by the present invention;

[0020] Figure 3 A schematic diagram of the power factor correction unit circuit structure provided by the present invention;

[0021] Figure 4 Functional diagram of the output synchronization following unit provided by the present invention;

[0022] Figure 5The output synchronization follower unit structure diagram provided by the present invention;

[0023] Figure 6 A schematic diagram of the resonant controller drive circuit structure provided by the present invention;

[0024] Figure 7 The LCC circuit structure diagram provided by the present invention;

[0025] Figure 8 Functional block diagram of the power output unit provided by the present invention;

[0026] Figure 9 A schematic diagram of the power output circuit structure provided by the present invention;

[0027] Figure 10 This is a schematic diagram of the ADC, DAC, and voltage measurement circuit structure provided by the present invention;

[0028] Figure 11 The charging and discharging power circuit structure diagram provided by the present invention;

[0029] Figure 12 The output protection switch and output protection control circuit structure diagram provided by the present invention;

[0030] Figure 13 The structural diagram of the current detection circuit, current range switching switch and current range control circuit provided by the present invention;

[0031] Figure 14 This is a schematic diagram of the differential pressure and optocoupler control circuit structure provided by the present invention;

[0032] Figure 15 A schematic diagram of the voltage adjustment and optocoupler control circuit provided by the present invention.

[0033] In the diagram: VCC1, first DC current; VCC2, second DC current; VCC3, third DC current; VCC4, fourth DC current; VCC5, fifth DC current; VO, final DC current. Detailed Implementation

[0034] To make the objectives, technical solutions, and advantages of this invention clearer, the invention will be further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative and not intended to limit the invention.

[0035] In this application, the term "switching transistor" is used. Switching transistor is a general term for MOS transistors, bipolar transistors, and IGBTs. In the embodiments, NMOS transistors are usually used as an example. The drain is defined as its first switching terminal, the source as its second switching terminal, and the gate as its controlled terminal.

[0036] See Figures 1 to 15 This invention provides a high-power analog battery, including a power factor correction unit, an output synchronization follower unit, and a power output unit. The power factor correction unit converts the input AC mains power into a high-voltage first DC voltage VCC1 and corrects its power factor, improving the power factor and reducing reactive current. The output synchronization follower unit obtains the first DC voltage VCC1 from the power factor correction unit and outputs a third DC voltage VCC3 ranging from 2 to 52V. The power output unit obtains the third DC voltage VCC3, outputs a final DC voltage VO, and feeds back the final DC voltage VO to the output synchronization follower unit. This ensures that when the output synchronization follower unit adjusts or fixes the voltage by following the voltage difference of the regulating transistor in the power output unit, it always maintains a fixed voltage, reducing the power consumption of the regulating transistor itself, improving the stability of the high-power analog battery system, meeting the current testing requirements for increased battery capacity, reducing heat generation, facilitating heat dissipation of components and optimization of heat sinks, and further reducing the size and weight of the high-power analog battery itself, making it lighter and more portable.

[0037] Inductive or capacitive loads cause the power factor of the power grid to be less than 1. An excessively low power factor wastes the capacity of the power supply equipment. This invention provides a power factor correction unit to correct the power factor.

[0038] See Figure 3 The power factor correction unit has a PFC module, which includes a first common-mode inductor for connection to AC mains power, a second common-mode inductor connected to the first common-mode inductor, and a rectifier module connected to the second common-mode inductor. A coil L1A is connected to the positive terminal of the rectifier module. The output terminal of coil L1A is connected to the drain of a switching transistor Q1, the source of transistor Q1 is grounded, and the gate of transistor Q1 is connected to the drive terminal of the power factor controller. Transistor Q1, coil L1A, capacitor C1, and the power factor controller constitute a power factor correction circuit. When transistor Q1 is turned on, current flows through coil L1A. Before coil L1A saturates, the current increases linearly, and electrical energy is stored in coil L1A in the form of magnetic energy. At this time, capacitor C1 discharges to provide energy to the load in the subsequent stage. When transistor Q1 is turned off, a self-induced electromotive force is generated across coil L1A to maintain the current direction. Thus, the self-induced electromotive force is connected in series with the power output from the rectifier module to supply power to capacitor C1 and the load.

[0039] Preferably, the switching transistor Q1 is an NMOS transistor.

[0040] The resulting benefits are: the input current is completely continuous and can be modulated throughout the sinusoidal period of the input voltage, thus achieving a high power factor; the current of coil L1A is the input current, which is easy to adjust; the gate drive signal ground of the switch Q1 is the same as the output ground, making driving simple; the input current is continuous, the peak current of the switch Q1 is small, and it is highly adaptable to changes in input voltage, even in situations where the mains voltage varies greatly.

[0041] See Figure 2 The power factor correction unit includes an auxiliary power supply for generating a low-voltage second DC current VCC2 to power the power factor controller.

[0042] To avoid surge current generated during power-on, a power-type thermistor is connected in series in the AC circuit of the rectifier module, specifically between the first and second common-mode inductors. This thermistor is a negative temperature coefficient thermistor, meaning its resistance decreases as temperature increases. When the load is too heavy, the current flowing through the thermistor increases, causing its temperature to rise. To prevent the thermistor from burning out due to overheating, a first voltage feedback circuit is also provided. This circuit collects the voltage of the first DC current VCC1. The output of the first voltage feedback circuit is connected to a switching transistor Q2, specifically to its base. The emitter of Q2 is grounded. A relay is connected in parallel with the thermistor, with its two normally open contacts connected to the two ends of the thermistor. The relay coil is connected to the low-voltage DC current VCC2 and the collector of the switching transistor Q2, respectively. The switching transistor Q2 controls the opening and closing of the relay. When the output current is too high, the switch inside the relay closes, short-circuiting the thermistor and preventing it from burning out.

[0043] Preferably, the switching transistor Q2 is an NPN transistor.

[0044] In one embodiment, the typical value of the high-voltage DC voltage VCC1 is 390V, and the typical value of the low-voltage DC voltage VCC2 is 12V.

[0045] See Figure 4 The output synchronization follower unit includes an input port connected to the output port of the power factor correction unit, which obtains the first DC power VCC1 and the second DC power VCC2 from the power factor correction unit. It also includes a control input port connected to the power output unit, which provides 12V power and control signals, and finally outputs the third DC power VCC3 to the power output unit.

[0046] See Figure 5The output synchronous follower unit includes a primary auxiliary power supply and a secondary auxiliary power supply. The primary auxiliary power supply converts the second DC voltage VCC2 into a fourth DC voltage VCC4 to power the resonant controller. The 12V of the control input port powers the secondary auxiliary power supply, which converts it into a fifth DC voltage VCC5 and a 2.5V voltage to power the voltage and current feedback circuit. The control signal is used for the optocoupler control circuit.

[0047] See Figure 6 The output synchronous follower unit includes a resonant controller for outputting a 50% duty cycle, with the high and low ends inverted by 180 degrees at the same time. The resonant controller is connected to a first DC power supply VCC1 and a fourth DC power supply VCC4, outputs a voltage drive signal SQH, and includes multiple controlled terminals controlled by an optocoupler control circuit, which is connected to the controlled terminals. The high-side floating gate drive output pin of the resonant controller is connected to the base of a PNP transistor Q8, and the low-side gate drive output pin is connected to the base of a PNP transistor Q7. The emitter of transistor Q8 is connected to the gate of a switching transistor Q4, and the drain of switching transistor Q4 is connected to the first DC power supply VCC1. The emitter of transistor Q7 is connected to the gate of switching transistor Q6, and the drain of switching transistor Q6 is connected to the source of switching transistor Q4. The source of switching transistor Q4 is grounded, and the collector of transistor Q7 is grounded. The floating ground pin of the high-side gate drive of the resonant controller is connected to the collector of transistor Q8 and the source of switching transistor Q4, respectively. This circuit modulates the first DC power supply VCC1 to generate the voltage drive signal SQH.

[0048] See Figure 7 The voltage drive signal SQH is input to the LCC circuit, which includes a synchronous rectifier controller U8. The voltage drive signal SQH is input to the transformer T3B, which has a primary coil LR3 and secondary coils T3D and T3E with a center tap. One end of the primary coil LR3 is connected to the voltage drive signal SQH, and the other end of the primary coil LR3 is grounded through the X capacitor CR3, which is used to eliminate differential mode interference. The two ends of the secondary coil are respectively connected to the drain of the switching transistor Q13 and the drain of the switching transistor Q14. The center tap is used to output a third DC power VCC3 from 2 to 52V.

[0049] The first drain terminal of the synchronous rectifier controller U8 is connected to the drain of the switching transistor Q14, the first gate terminal is connected to the gate of the switching transistor Q14, and the first source terminal is connected to the source of the switching transistor Q14; the second drain terminal of the synchronous rectifier controller U8 is connected to the drain of the switching transistor Q13, the second gate terminal is connected to the gate of the switching transistor Q13, and the second source terminal is connected to the source of the switching transistor Q13.

[0050] The LCC circuit also includes a primary-side current sampling circuit, which samples the current on the primary side of transformer T3B and feeds it back to the resonant controller. The primary-side current sampling circuit includes a resistor R68 connected to the other end of the primary-side coil LR3. Resistor R68 is connected to the middle node of a switching diode D5 used to suppress conducted interference via a series capacitor C6. Switching diode D5 consists of two diodes connected end-to-end. The anode of switching diode D5 is grounded, and the cathode of switching diode D5 is connected to the current detection signal input terminal of the resonant controller via the CS line.

[0051] Furthermore, the cathode of the switching diode D5 is also connected to a resistor-capacitor filter circuit, which is grounded through resistor R75, capacitor R79 and capacitor C21 respectively. The parallel resistor R75, capacitor R79 and capacitor C21 constitute the resistor-capacitor filter circuit.

[0052] The LCC circuit described above includes multiple identical circuits, which are connected in parallel to increase the output power and output stability.

[0053] See Figure 5 The voltage and current feedback circuit includes a voltage feedback circuit and a current feedback circuit. The optocoupler control circuit includes a first optocoupler, a second optocoupler, and a third optocoupler. The control input port controls the first optocoupler through the PS_ON line. The secondary auxiliary power supply provides 2.5V power to the voltage feedback circuit. The control input port controls the second optocoupler through the third DC power supply VCC3 and the final DC power supply VO. The output terminals of the second and third optocouplers are connected in parallel. The output terminal of the third optocoupler is connected to the intermittent working mode threshold pin and the minimum oscillation frequency setting pin of the resonant controller, respectively.

[0054] The voltage feedback circuit detects the voltage value of the third DC power supply VCC3 and controls the primary auxiliary power supply through the first optocoupler, causing the primary auxiliary power supply to output or shut down the fourth DC power supply VCC4. When an overvoltage is detected in the third DC power supply VCC3, the primary auxiliary power supply shuts down its output, thus achieving overvoltage protection.

[0055] The current detection circuit detects the current value of the third DC power supply VCC3 and feeds it back to the resonant controller through the third optocoupler, which can enable the resonant controller to work or standby, thus achieving intermittent operation.

[0056] See Figure 8The power output unit includes a power output circuit, an MCU, an ADC, a DAC, a communication circuit, a power control interface, and a voltage measurement circuit. The MCU is used for the overall system control of the power output circuit; the ADC is used for analog-to-digital signal conversion; the DCA is used for digital-to-analog signal conversion; the communication circuit is used for communication between the MCU and external devices; the power control interface is used to provide control signals; the voltage measurement circuit is used to measure the voltage output by the power output circuit; and the control input port serves as a shared interface, connecting to both the power output unit and the output synchronization follower unit, and is used to provide voltage and control signals, including control signals such as Ct1_Up and Ct1_Down.

[0057] The power output circuit can be used for discharging and charging. Here, discharging refers to the power output circuit providing voltage to external electrical equipment for operation; charging refers to the power output unit consuming electrical energy as a load to complete the charging function test of the product under test.

[0058] See Figure 9 The power output circuit includes a discharge power adjustment tube located at the top and a charging power adjustment tube located at the bottom. The power input terminal of the discharge power adjustment tube is used to connect to the third DC power VCC3 of the output synchronous follower unit. Controlled by the Ct1_Up signal line, the discharge power adjustment tube switches according to a predetermined frequency. The Output_V line obtains the voltage and finally outputs the DC power VO to provide power to external electrical equipment.

[0059] During charging, an external voltage is introduced into the Output_V line of the power output circuit. Controlled by the Ct1_Down signal line, the charging power adjustment tube switches on and off according to a predetermined frequency. The charging power adjustment tube consumes electrical energy, thus completing the charging test of the product under test.

[0060] Specifically, such as Figure 11 As shown, the discharge power adjustment transistor includes a switching transistor Q15. The drain of the switching transistor Q15 is used to input the third DC power VCC3. The source of the switching transistor Q15 is connected to the Output_V line through a resistor R19. The gate of the switching transistor Q15 is connected to the Ct1_Up signal line. When the Ct1_Up signal line is high, the switching transistor Q15 is turned on, and the third DC power VCC3 falls into the Output_V line, thereby discharging to the outside.

[0061] Furthermore, to improve output power and stability, a switching transistor Q16 is included, controlled by the turn-on of switching transistor Q15. The drain of switching transistor Q16 is used to input the third DC current VCC3, the source of switching transistor Q16 is connected to the Output_V line through resistor R32, and the gate of switching transistor Q16 is connected to the output of comparator U6. The inverting input of comparator U6 obtains a reference voltage from the Clt_VCC line through resistor R26. The non-inverting input of comparator U6 is connected to the source of switching transistor Q15, the positive terminal of comparator U6 is connected to the Clt_VCC line, and the negative terminal of comparator U6 is connected to the Output_V line. When switching transistor Q15 is turned on, the high-level output of comparator U6 turns on switching transistor Q16, increasing the path of the third DC current VCC3 to the Output_V line. Resistors R19 and R32 have very low resistance and can carry large currents; they are preferably alloy resistors.

[0062] During discharge, switch Q15 turns on first, followed by switch Q16. This delay avoids the current surge caused by simultaneous conduction. In addition, switch Q16 can be controlled independently via Ctl_VCC to control the number of conducting switches and thus the output power. Switches Q15 and Q16 are linearly adjustable power transistors, improving the output voltage quality.

[0063] The combination circuit of switching transistor Q16 and comparator U6 can be increased, further increasing the path of the third DC current VCC3 to the Output_V line, thereby increasing the output current, enhancing the stability of the output, and increasing the output power.

[0064] The charging power adjustment transistor includes a switching transistor Q17. The drain of the switching transistor Q17 is used to input the voltage of the Output_V line. That is, when the product under test is testing its charging function, the Output_V line is the power supply voltage of the product under test. The source of the switching transistor Q17 is connected to the ground GND through a resistor R27. The gate of the switching transistor Q17 is connected to the Ct1_Down signal line. When the Ct1_Down signal line is high, the switching transistor Q17 is turned on, and the power supply of the product under test falls to the ground GND, thereby consuming electrical energy.

[0065] Furthermore, to improve load capacity, a switching transistor Q18 is included, controlled by the on-state of switching transistor Q17. The drain of switching transistor Q18 is used to input the voltage of the Output_V line, the source of switching transistor Q18 is connected to ground GND through resistor R33, and the gate of switching transistor Q18 is connected to the output of comparator U7. The inverting input of comparator U7 obtains a reference voltage from the 12V power supply through resistor R31, the non-inverting input of comparator U7 is connected to the source of switching transistor Q17, the positive terminal of comparator U7 is provided with a 12V voltage, and the negative terminal of comparator U7 is connected to ground GND. When switching transistor Q17 is turned on, the high-level output of comparator U7 turns on switching transistor Q18, increasing the path for the voltage of the Output_V line to be applied to ground GND. Resistors R27 and R33 have extremely low resistance and can carry large currents; they are preferably alloy resistors.

[0066] The combination circuit of switch Q18 and comparator U7 can be increased, further increasing the path of voltage applied to ground GND on the Output_V line, improving load capacity, enhancing load stability, and increasing load power.

[0067] Switches Q15, Q16, Q17, and Q18 are preferably linear power NMOS transistors, which can effectively suppress glitches and interference generated by the DC / DC switching output of analog batteries, improve the speed of dynamic response, reduce output voltage noise interference, and ensure pure and stable voltage, thereby improving the quality and efficiency of analog battery test products. The average current magnitude is changed by altering the duty cycle of the Ct1_Up and Ct1_Down signal lines.

[0068] See Figure 9 A current-sensing resistor is connected in series with the ground wire GND. The voltage across the current-sensing resistor is acquired by the output current amplifier circuit and sent to the MCU. The current-sensing resistor includes a first current-sensing resistor for detecting current in the ampere level and a second current-sensing resistor for detecting current in the milliampere level.

[0069] A current range selector switch is also provided on the ground wire GND. The current range selector switch is connected in parallel with the second current sensing resistor. The MCU controls the current range selector switch through the current range control circuit. When the current range selector switch is open, the current in the circuit is small, and the second current sensing resistor plays a major role, making the current detection more accurate. When the current range selector switch is closed, a larger current can flow through the circuit, the second current sensing resistor is short-circuited, and the second current sensing resistor has no effect. The current range selector switch is opened or closed according to different application scenarios.

[0070] The current range switch can be switched automatically or manually, preferably automatically by MCU control. In automatic mode, the current is detected by the output current amplifier circuit as the basis for judgment. When the current decreases to a predetermined value, it automatically switches to a low current range to simulate the voltage change of the battery during charging and discharging over a certain period of time, which also makes the current measurement more accurate and is very convenient for testing the static current and power consumption of the product. In manual mode, it can be set through the control panel and adjusted according to the user's needs.

[0071] Specifically, see Figure 13 Resistor R41 is the first current sensing resistor, resistor R40 is the second current sensing resistor, switching transistors Q23 and Q24 constitute a current range switching switch, and transistors Q26 and Q27, resistors R38 and R39 constitute a current range control circuit.

[0072] It is understandable that in order to increase the output current and improve the output power in the circuit, multiple switching transistors can be connected in parallel with switching transistors Q23 and Q24 respectively.

[0073] Preferably, switching transistors Q23 and Q24 are NMOS transistors.

[0074] Furthermore, a capacitor C11 is connected in parallel between the drain and source of the switching transistor Q23 to reduce switching spikes and reduce electromagnetic radiation.

[0075] When the MCU generates a low level through port A / mA, transistor Q26 is cut off, the base of transistor Q27 obtains voltage through pull-up resistor R38, transistor Q27 turns on, and the gates of switching transistors Q23 and Q24 obtain the turn-on voltage and turn on, that is, the current range switch is closed, the second current sensing resistor is short-circuited, and a large current can flow through the circuit. The first current sensing resistor detects the ampere-level current in the circuit and feeds it back to the MCU through the output current amplification circuit.

[0076] When the MCU generates a high level through port A / mA, transistor Q26 is turned on, grounding the base of transistor Q27. Transistor Q27 is turned off, and the gates of switching transistors Q23 and Q24 lose their turn-on voltage and are turned off. That is, the current range switch is turned off, and the current flows through the second current sensing resistor. A small current flows through the circuit, and the second current sensing resistor detects the milliampere-level current in the circuit and feeds it back to the MCU through the output current amplification circuit.

[0077] To detect the charging and discharging currents separately, the output current amplifier circuit includes operational amplifiers U9-A and U9-B. The first terminal of the first current-sensing resistor (R41) is connected to the inverting input of operational amplifier U9-A and the non-inverting input of operational amplifier U9-B, respectively. The second terminal of the first current-sensing resistor (R41) is also connected to the non-inverting input of operational amplifier U9-A and the inverting input of operational amplifier U9-B, respectively. The first terminal of the second current-sensing resistor (R40) is connected to the non-inverting input of operational amplifier U9-A and the inverting input of operational amplifier U9-B, respectively. The second terminal of the second current-sensing resistor (R40) is connected to the non-inverting input of operational amplifier U9-A and the inverting input of operational amplifier U9-B through diodes D3 and D4 connected in reverse parallel. This achieves current amplification from different current directions.

[0078] See Figure 9 An output protection switch is also provided on the ground line GND. Based on the current detected by the output current amplification circuit, the MCU controls the output protection switch through the output protection control circuit. When the current is too large and exceeds the threshold, the output protection switch is turned off.

[0079] See Figure 12 The output protection switch includes switching transistors Q19 and Q20. The drain of switching transistor Q19 is connected to the circuit at the front end of the protection, and the source of switching transistor Q19 is connected to the source of switching transistor Q20. The drain of switching transistor Q20 is the output circuit at the back end of the protection. The gates of switching transistors Q19 and Q20 are connected to the output protection control circuit.

[0080] The output protection control circuit includes optocouplers Q21 and Q22. The emitter of optocoupler Q21 is connected to the source of switching transistor Q19, and the collector of optocoupler Q21 is connected to the gates of switching transistors Q19 and Q20 respectively. The emitter of optocoupler Q22 is connected to the collector of optocoupler Q21 through resistor R37, and the collector of optocoupler Q22 is set with a voltage of 12V. The cathode of optocoupler Q22 is grounded, and the anode of optocoupler Q22 is connected to the cathode of optocoupler Q21 through two series resistors R35 and R36. The anode of optocoupler Q21 is set with a voltage of 3.3V, and the intermediate node of resistors R35 and R36 is connected to the OUT port of the MCU.

[0081] The MCU generates high and low levels through its OUT port, causing optocouplers Q21 and Q22 to work alternately. When optocoupler Q21 is working, its internal transistor is turned on, causing the voltage of switching transistors Q19 and Q20 to change. GS V is 0 GS <V THWhen switching transistors Q19 and Q20 are off, the output protection switch is open, providing protection. When optocoupler Q22 is working, its internal transistor is turned on, allowing the gates of switching transistors Q19 and Q20 to receive voltage, V. GS >V TH When switching transistors Q19 and Q20 are turned on, the output protection switch is closed, forming a circuit.

[0082] Furthermore, multiple switching transistors can be connected in parallel with switching transistors Q19 and Q20 respectively to increase the output current and improve the output power.

[0083] It is understandable that the aforementioned current sensing resistor, current range switch, and output protection switch can also be set on the Output_V line.

[0084] like Figure 9 As shown, conventional analog batteries use an MCU directly connected to the output current amplifier circuit, so the MCU directly samples the analog quantity, which has the advantage of fast response speed. However, due to the characteristics of the MCU itself, the display accuracy is not high.

[0085] like Figure 10 As shown, in order to provide accuracy in current display, a current signal ADC is provided to convert the analog current quantity into a digital quantity. The input terminal of the current signal ADC is connected to both ends of the current sensing resistor, and the output terminal of the current signal ADC is connected to the MCU. The sampled signal is sent to the MCU after being sampled by a separate high-precision current signal ADC, which can improve the sampling accuracy.

[0086] Furthermore, the current signal ADC includes an ampere ADC and a milliampere ADC, the input terminals of which are connected to the two ends of the first current sensing resistor and the second current sensing resistor, respectively.

[0087] The voltage measurement circuit includes a local output sampling circuit and a remote output sampling circuit. The local output sampling circuit is used to take the output voltage of the local port. Since the transmission line of the product under test is too long, there is a voltage drop on the transmission line. The displayed voltage does not represent the true voltage value obtained by the product under test. Therefore, a remote output sampling circuit is also provided to solve the problem of large current voltage drop.

[0088] Furthermore, to improve the accuracy of voltage measurement, a voltage signal ADC is also included, which allows for more precise sampling and more accurate display.

[0089] The parameters controlled by the display screen, or the parameter settings from external host computers, ATE test cabinets, etc., are sent to the MCU via the communication circuit. After being processed by the MCU and converted by the DAC, they are sent to the power output circuit to control the output voltage.

[0090] Preferably, the communication circuit is an RS485 communication circuit.

[0091] See Figure 14 To address the voltage difference issue of the discharge power adjustment transistor in the power output circuit, the optocoupler control circuit obtains the third DC voltage VCC3 and the final DC voltage VO from the power output unit. Because of the voltage difference in the discharge power adjustment transistor, the voltage of the final DC voltage VO will be lower than that of the third DC voltage VCC3. When the voltage difference between the two is lower than the threshold, the second optocoupler Q30 operates, and the transistor in the second optocoupler Q30 conducts, pulling down the relevant power pins of the resonant controller. This causes the resonant controller to adjust the output frequency, thereby changing the third DC voltage VCC3 and the final DC voltage VO. In other words, when the output synchronization follower unit adjusts or operates at a fixed voltage following the voltage difference of the adjustment transistor in the power output unit, it always maintains a fixed voltage, reducing the power consumption of the power adjustment transistor itself, improving the stability of the high-power analog battery system, meeting the current testing requirements for increased battery capacity, reducing heat generation, and facilitating the optimization of component heat dissipation and heat sinks. This, in turn, reduces the size and weight of the high-power analog battery itself, making it lighter and more portable.

[0092] Specifically, the collector of the second optocoupler Q30 is connected to the resonant controller, the emitter of the second optocoupler Q30 is connected to ground HGND, the anode of the second optocoupler Q30 is connected to the third DC current VCC3 through a constant current circuit, and the cathode of the second optocoupler Q30 is connected to the terminal DC current VO. The voltage difference between the third DC current VCC3 and the terminal DC current VO constitutes an external voltage difference signal, which the constant current circuit limits, improving control accuracy. The constant current circuit includes NPN transistors Q31 and Q32. The base of transistor Q31 is connected to the emitter of transistor Q32, and the collector of transistor Q31 is connected to the base of transistor Q32. A resistor R46 for current sampling is provided between the base and emitter of transistor Q31. The emitter of transistor Q31 is connected to the anode of the second optocoupler Q30, and the base of transistor Q32 is connected to the DC switching power supply through a bias resistor R47.

[0093] In addition, see Figure 15The voltage adjustment circuit obtains the third DC power VCC3 from the power output unit and feeds it back to the resonant controller through comparator U10 and optocoupler Q33 to adjust the oscillation frequency of the resonant controller, thereby achieving voltage adjustment. The non-inverting input of comparator U10 obtains a divided voltage from the third DC power VCC3 through a resistor divider circuit composed of resistors R49 and R50. The inverting input of comparator U10 is provided with a reference voltage. The output of comparator U10 is connected to the anode of optocoupler Q33 through resistor R51. The cathode of optocoupler Q33 is grounded. The collector of optocoupler Q33 is connected to the resonant control of the output synchronous follower unit. The emitter of optocoupler Q33 is grounded.

[0094] In summary, the high-power analog battery provided by this invention improves upon the shortcomings of existing technologies. The output voltage drive signal waveform of the resonant controller of the output synchronization follower unit is fed to the LCC circuit for power conversion. After conversion by the LCC circuit, a voltage is provided for the output. The voltage and current signals at the output terminal are fed to the voltage and current feedback circuit. The voltage and current feedback signals are transmitted to the feedback terminal of the resonant controller through the optocoupler control circuit, thereby controlling the voltage and current output of the power supply. The output voltage signal of the power output unit is input to the optocoupler control circuit to control the voltage of the output synchronization follower unit to follow the output voltage of the entire high-power analog battery. The pre-stage power supply uses an adjustable LCC switching power supply, which can significantly reduce the size and weight of high-power instruments. Voltage following adjustment can increase the adjustable voltage range of the analog battery output. The analog battery power output uses a linearly adjustable power transistor to improve the output voltage quality.

[0095] The above description is only a preferred embodiment of the present invention and is not intended to limit the present invention. Any modifications, equivalent substitutions, and improvements made within the spirit and principles of the present invention should be included within the protection scope of the present invention.

Claims

1. A high-power analog battery comprising a power output unit for outputting a terminal direct current (VO), characterized by, It also includes an output synchronization follower unit for outputting a third DC power (VCC3). The power output unit includes a power output circuit. The power input terminal of the power output circuit is connected to the power output terminal of the output synchronization follower unit. The power output circuit is equipped with a discharge power adjustment tube. The output synchronization follower unit dynamically adjusts the output of the third DC power (VCC3) according to the voltage difference signal between the input and output terminals of the discharge power adjustment tube. in, An optocoupler control circuit for feedback of the differential pressure signal is provided between the power output unit and the output synchronization follower unit; The output synchronization follower unit includes an LCC circuit for power conversion, a resonant controller for providing a voltage drive signal to the LCC circuit, an optocoupler control circuit that feeds back the differential voltage signal to the resonant controller, and the LCC circuit that outputs a third DC current (VCC3) to the power output unit.

2. The high-power simulated battery according to claim 1, characterized in that, The output synchronization follower unit also includes a voltage and current feedback circuit for feeding back the parameters of the third DC current (VCC3) to the resonant controller.

3. The high-power simulated battery according to claim 2, characterized in that, The LCC circuit includes a transformer, a synchronous rectifier controller, and switching transistors Q13 and Q14 controlled by the synchronous rectifier controller. The primary side of the transformer is used for input voltage drive signals, and the secondary side of the transformer is provided with a center tap for outputting a third DC power (VCC3). The two ends of the secondary side are respectively connected to the first switching terminals of switching transistors Q13 and Q14. The second switching terminals of switching transistors Q13 and Q14 are respectively connected to the synchronous rectifier controller. The controlled terminals of switching transistors Q13 and Q14 are respectively connected to the synchronous rectifier controller.

4. The high-power simulated battery according to claim 3, characterized in that, The LCC circuit also includes a primary-side current sampling circuit for feeding back the primary-side current to the resonant controller.

5. The high-power simulated battery according to claim 1, characterized in that, The discharge power adjustment transistor includes a switching transistor Q15 and a switching transistor Q16 controlled by the switching transistor Q15. The controlled terminal of the switching transistor Q16 is connected to the output terminal of the comparator U6. The non-inverting input terminal of the comparator U6 is connected to the second switching terminal of the switching transistor Q15. The inverting input terminal of the comparator U6 is provided with a reference voltage. The first switching terminals of the switching transistors Q15 and Q16 are input with a third DC current (VCC3). The second switching terminals of the switching transistors Q15 and Q16 are used to output the final DC current (VO).

6. The high-power simulated battery according to claim 5, characterized in that, The power output unit also includes a charging power adjustment tube used for load testing, and the output line of the power output circuit is also connected in series with a current sensing resistor, a current range switching switch and an output protection switch.

7. The high-power simulated battery according to claim 6, characterized in that, It also includes a voltage adjustment circuit for obtaining a third DC power (VCC3) from the power output unit and feeding it back to the output synchronization follower unit through comparator U10 and optocoupler Q33.

8. The high-power simulated battery according to any one of claims 1 to 7, characterized in that, The system includes a power factor correction unit (PFC) for providing a first DC voltage (VCC1) to the output synchronous follower unit. The PFC module includes a first common-mode inductor connected to the mains power supply, a second common-mode inductor connected to the first common-mode inductor, and a rectifier module connected to the second common-mode inductor. The positive terminal of the rectifier module is connected to the input terminal of coil L1A. The output terminal of coil L1A is connected to the first switching terminal of a switching transistor Q1, and the second switching terminal of switching transistor Q1 is grounded. The controlled terminal of switching transistor Q1 is connected to the driving terminal of a power factor controller. The output terminal of coil L1A is grounded through capacitor C1. Switch Q1, coil L1A, capacitor C1, and the power factor controller constitute a power factor correction circuit. A thermistor is connected in series in the AC circuit preceding the rectifier module, and a relay is connected in parallel to the thermistor. A switching transistor Q2 is also provided for controlling the opening and closing of the relay. Switch Q2 is connected to a first voltage feedback circuit for controlling its conduction and cutoff. The first voltage feedback circuit is used to sample the first DC voltage (VCC1).

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