Switched-capacitor voltage conversion circuit and switched-capacitor voltage conversion method

Abstract

A switched-capacitor voltage conversion circuit and a switched-capacitor voltage conversion method. The switched-capacitor voltage conversion circuit includes a switched-capacitor converter and a control circuit. The control circuit adjusts an operating frequency and / or a duty cycle of a first and / or a second operating signal to adjust a ratio between a first voltage and a second voltage to a predetermined ratio. When the control circuit reduces the duty cycle of the first and / or the second operating signal, in the first and / or the second procedure, if a plurality of switches of the switched-capacitor converter are turned on, an inductor current flowing toward the second voltage is in a first state, and if an inductor current flowing through a corresponding inductor is freewheeled through at least one freewheeling path, the inductor current flowing toward the second voltage is in a second state, so that the corresponding inductor performs inductive power conversion switching between the first state and the second state.

Description

Technical Field

[0001] This invention relates to a switching capacitor voltage conversion circuit, and more particularly to a switching capacitor voltage conversion circuit and a switching capacitor voltage conversion method capable of adjusting the ratio of input voltage to output voltage. Background Technology

[0002] Figure 1 This illustrates a known buck converter circuit 10. The inductor L of this known buck converter circuit 10 needs to withstand voltage stress at the input voltage level, necessitating a large inductor size and a high inductance value. Generally, a higher switching frequency allows for a smaller inductor size in the converter circuit. However, switching power losses also increase significantly with higher switching frequencies and higher input voltages for the switch.

[0003] In view of this, the present invention addresses the shortcomings of the prior art by proposing an innovative switching capacitor voltage conversion circuit. Summary of the Invention

[0004] In one viewpoint, the present invention provides a switching capacitor voltage conversion circuit for converting a first voltage to a second voltage or converting the second voltage to the first voltage. The switching capacitor voltage conversion circuit includes: a switching capacitor converter coupled between the first voltage and the second voltage; and a control circuit for generating a control signal to control the switching capacitor converter, thereby converting the first voltage to the second voltage or the second voltage to the first voltage; wherein the switching capacitor converter includes: at least one resonant capacitor; a plurality of switches coupled to the at least one resonant capacitor; and at least one inductor; wherein the control circuit generates the control signal, the control signal including a... A first operation signal and a second operation signal are used, wherein the first operation signal is used to operate a plurality of first switches of the plurality of switches, and the second operation signal is used to operate a plurality of second switches of the plurality of switches; wherein, in a first procedure, the switching of the plurality of first switches is controlled by the first operation signal, so that at least one resonant capacitor and the corresponding inductor are connected in series between the first voltage and the second voltage to form a first current path and resonate; wherein, in at least one second procedure, the switching of the plurality of second switches is controlled by the second operation signal, so that at least one resonant capacitor and the corresponding inductor are connected in series between the second voltage and the DC potential, thereby simultaneously or alternately forming a plurality of second current paths. The circuit operates in a flow path and resonant mode; wherein the conduction periods of the plurality of first switches and the conduction periods of the plurality of second switches do not overlap, so that the first program and the second program do not overlap; wherein the control circuit adjusts the operating frequency and / or duty cycle of the first operation signal and / or the second operation signal according to a preset ratio, thereby adjusting the ratio between the first voltage and the second voltage to the preset ratio; wherein the first program and the at least one second program are repeatedly and alternately ordered to convert the first voltage to the second voltage or the second voltage to the first voltage; wherein when the control circuit reduces the duty cycle of the first operation signal and / or the second operation signal according to the preset ratio... Duty cycle, in the first program and / or the second program, when the plurality of first switches and / or the plurality of second switches are turned on, the inductor current flowing toward the second voltage is in a first state, wherein the inductor current flowing toward the second voltage in the first state is a resonant current. When the control circuit reduces the duty cycle of the first operation signal and / or the second operation signal according to the preset ratio, in the first program and / or the second program, the inductor current flowing through the corresponding inductor continues to flow through a current freewheeling path, thereby causing the inductor current flowing toward the second voltage to be in a second state, so that the corresponding inductor performs inductive power conversion switching between the first state and the second state.

[0005] In another viewpoint, the present invention provides a switching capacitor voltage conversion method for converting a first voltage to a second voltage or vice versa. The switching capacitor voltage conversion method includes: operating a plurality of first switches with a first operation signal; operating a plurality of second switches with a second operation signal; in a first procedure, controlling the switching of the plurality of first switches via the first operation signal, such that at least one resonant capacitor and a corresponding inductor are connected in series between the first voltage and the second voltage to form a first current path and resonant operation; in at least a second procedure, controlling the switching of the plurality of second switches via the second operation signal, such that at least one resonant capacitor and the corresponding inductor are connected in series between the second voltage and a DC potential, thereby simultaneously or alternately forming a plurality of second current paths and resonant operation; and adjusting the operating frequency and / or duty cycle of the first operation signal and / or the second operation signal according to a preset ratio, thereby adjusting the ratio between the first voltage and the second voltage to the preset ratio; wherein the conduction period of the plurality of first switches... The conduction periods of the first program and the second program do not overlap with each other, so that the first program and the second program do not overlap with each other; wherein the first program and the at least one second program are repeatedly and alternately sorted to convert the first voltage to the second voltage or the second voltage to the first voltage; wherein when the duty cycle of the first operation signal and / or the second operation signal is reduced according to the preset ratio, in the first program and / or the second program, and when the multiple first switches and / or the multiple second switches are turned on, the inductor current flowing toward the second voltage is in a first state, wherein the inductor current flowing toward the second voltage in the first state is a resonant current; when the duty cycle of the first operation signal and / or the second operation signal is reduced according to the preset ratio, in the first program and / or the second program, the inductor current flowing through the corresponding inductor continues through a current freewheeling path, thereby making the inductor current flowing toward the second voltage in a second state, so that the corresponding inductor performs inductive power conversion switching between the first state and the second state.

[0006] In one embodiment, when the duty cycle of the first operation signal and / or the second operation signal is reduced according to the preset ratio, and during the first program and / or the second program, when neither of the plurality of first switches nor the plurality of second switches is turned on, one end of the corresponding inductor is turned on to the DC potential through the body diode of at least one of the plurality of first switches and the plurality of second switches, so that the inductor current flowing toward the second voltage is the linear ramp current, thereby adjusting the preset ratio.

[0007] In one embodiment, when the duty cycle of the first operation signal and / or the second operation signal is reduced according to the preset ratio, during the first program and / or the second program, and when neither of the plurality of first switches nor the plurality of second switches is turned on, the inductor current flowing through the corresponding inductor is continued through a closed loop formed by a resonant tank and the internal diode of the at least one of the plurality of first switches and the plurality of second switches via the conduction of the body diode, thereby causing the second state to be that the inductor current stops flowing toward the second voltage, wherein the at least one resonant capacitor and the corresponding inductor form the resonant tank.

[0008] In one embodiment, the switching capacitor voltage conversion method further includes providing a non-resonant capacitor coupled to the resonant capacitor, wherein the voltage across the non-resonant capacitor is maintained at a fixed DC voltage during the first and second processes.

[0009] In one embodiment, the switched capacitor voltage conversion method further includes providing a switched capacitor converter, which provides the plurality of first switches, the plurality of second switches, the at least one resonant capacitor, and the inductor, wherein the switched capacitor converter includes a distributed switched capacitor converter, a series-parallel switched capacitor converter, a Dickson switched capacitor converter, a ladder switched capacitor converter, a doubler switched capacitor converter, a Fibonacci switched capacitor converter, a piperined switched capacitor converter, or a switched tank converter.

[0010] In one embodiment, the switching capacitor voltage conversion method further includes: sensing the current flowing through the at least one inductor to generate at least one current sensing signal; and generating the first operating signal and / or the second operating signal based on the current sensing signal and the preset ratio.

[0011] In one embodiment, the second state is that the inductor current flowing toward the second voltage is a non-resonant current.

[0012] In one embodiment, the second state is that the inductor current stops flowing toward the second voltage, or the inductor current flowing toward the second voltage is a linear ramp current.

[0013] In one embodiment, when neither the plurality of first switches nor the plurality of second switches are turned on during the first procedure and / or the second procedure, the inductor current is in the second state, and the freewheeling path through which the current flows includes the body diode in the corresponding switch.

[0014] In one embodiment, when the control circuit reduces the duty cycle of the first operation signal and / or the second operation signal according to the preset ratio, and during the first program and / or the second program, when neither of the plurality of first switches nor the plurality of second switches is turned on, one end of the corresponding inductor is turned on to the DC potential through the body diode in at least one of the switches, so that the inductor current flowing toward the second voltage is the linear ramp current, thereby adjusting the preset ratio.

[0015] In one embodiment, when the control circuit reduces the duty cycle of the first operation signal and / or the second operation signal according to the preset ratio, and during the first program and / or the second program, when neither of the plurality of first switches nor the plurality of second switches is turned on, the inductor current flowing through the corresponding inductor continues through a closed loop formed by a resonant tank and the internal diode in the at least one switch, thereby causing the second state to be that the inductor current stops flowing toward the second voltage, wherein the at least one resonant capacitor and the at least one inductor form the resonant tank.

[0016] In one embodiment, during the first procedure and / or the second procedure, after the inductor current flowing through the corresponding inductor decreases to 0, the plurality of switches remain unconducted for a zero-current period.

[0017] In one embodiment, the switching capacitor voltage conversion circuit further includes a non-resonant capacitor coupled to the resonant capacitor, wherein the voltage across the non-resonant capacitor is maintained at a fixed DC voltage during the first and second processes.

[0018] In one embodiment, the first voltage is twice the second voltage, and the first operating signal and the second operating signal have their respective corresponding operating frequencies.

[0019] In one embodiment, the duty cycle of both the first operation signal and the second operation signal is 50%.

[0020] In one embodiment, the preset ratio is the ratio of the first voltage to the second voltage, and the operating frequency of the first operating signal and / or the second operating signal is positively correlated with the preset ratio.

[0021] In one embodiment, the operating frequency of the first operating signal is higher than the resonant frequency of the at least one resonant capacitor and the corresponding inductor in the first program, and the operating frequency of the second operating signal is higher than the resonant frequency of the at least one resonant capacitor and the corresponding inductor in the second program.

[0022] In one embodiment, the preset ratio is a positive integer not less than 2.

[0023] In one embodiment, the switching capacitor converter includes a distributed switched capacitor converter, a series-parallel switched capacitor converter, a Dickson switched capacitor converter, a ladder switched capacitor converter, a doubler switched capacitor converter, a Fibonacci switched capacitor converter, a piperined switched capacitor converter, or a switched tank converter.

[0024] In one embodiment, the series-parallel switched capacitor converter includes a 2-to-1 series-parallelswitched capacitor converter, a 3-to-1 series-parallel switched capacitor converter, or a 4-to-1 series-parallel switched capacitor converter.

[0025] In one embodiment, the DC potential is a ground potential.

[0026] In one embodiment, the control circuit includes: a current sensing circuit for sensing the current flowing through the at least one inductor to generate at least one current sensing signal; and a control signal generating circuit coupled to the current sensing circuit for generating the control signal based on the current sensing signal and the preset ratio.

[0027] The advantages of this invention are that by adjusting the duty cycle and / or operating frequency and allowing the inductor current to freewheel, it can improve power conversion efficiency, reduce switching losses, reduce voltage stress on the switch and inductor, reduce inductor size, and make the output voltage adjustable.

[0028] The following detailed description through specific embodiments will make it easier to understand the purpose, technical content, features and effects achieved by the present invention. Attached Figure Description

[0029] Figure 1 This is a schematic diagram of a known buck converter circuit.

[0030] Figure 2A This is a circuit diagram showing a switching capacitor voltage conversion circuit according to an embodiment of the present invention.

[0031] Figure 2B This is a circuit block diagram showing a control circuit for a switching capacitor voltage conversion circuit according to an embodiment of the present invention.

[0032] Figure 2C This is a circuit diagram showing a switching capacitor voltage conversion circuit according to an embodiment of the present invention.

[0033] Figure 3A This is a schematic diagram of the signal waveforms of a control circuit for a switching capacitor voltage conversion circuit according to an embodiment of the present invention.

[0034] Figure 3B This is a schematic diagram of the signal waveforms of a control circuit for a switching capacitor voltage conversion circuit according to an embodiment of the present invention.

[0035] Figure 3C This is a schematic diagram of the signal waveforms of a switching capacitor voltage conversion circuit according to an embodiment of the present invention.

[0036] Figure 3D This is a schematic diagram of the signal waveforms of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0037] Figure 3EThis is a schematic diagram of the signal waveforms of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0038] Figure 3F This is a schematic diagram of the signal waveforms of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0039] Figure 4 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0040] Figure 5 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0041] Figure 6 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0042] Figure 7 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0043] Figure 8 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0044] Figure 9 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0045] Figure 10 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0046] Figure 11 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0047] Figure 12 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0048] Figure 13 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0049] Figure 14 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0050] Figure 15 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0051] Figure 16 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0052] Figure 17 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0053] Figure 18 This is a circuit block diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0054] Figure 19 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0055] Figure 20 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0056] Figure 21 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0057] Figure 22A This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0058] Figure 22B This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0059] Figure 23 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0060] Figure 24 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0061] Figure 25 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0062] Figure 26 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0063] Figure 27 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0064] Figure 28 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0065] Figure 29 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0066] Figure 30 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention.

[0067] Explanation of symbols in the diagram

[0068] 10: Given a buck converter circuit

[0069] 20, 30, 30a, 30b, 40, 40a, 50, 50a, 50b, 60, 70, 80, 90, 100, 110, 110b, 120, 130, 140, 150, 160, 170, 180, 190, 200, 210, 220, 230: Switching capacitor voltage conversion circuit

[0070] 201, 301, 301a, 301b, 401, 401a, 501, 501a, 501b, 601, 701, 801, 901, 1001, 1101, 1201, 1301, 1401, 1501, 1601, 1701, 1801, 1901, 2001, 2101, 2201, 2301: Control circuit

[0071] 2011: Current Sensing Circuit

[0072] 2012: Control Signal Generation Circuit

[0073] 202, 302, 302a, 302b, 402, 402a, 502, 502a, 502b, 602, 1502, 1602, 1702, 1802, 1902, 2002, 2102, 2202, 2302: Switching Capacitor Converters

[0074] 4021, 4021a, 4022, 4022a, 7021, 7022, 7031, 7032, 11021, 11022, 11031, 11032, 15021, 15022: Resonant grooves

[0075] 4023, 4024, 4024a, 7023, 7024, 7033, 7034, 11023, 11024, 11033, 11034, 15023: Closed loop

[0076] 6021: Transformer

[0077] 702, 802, 902, 1002, 1102, 1102b, 1202, 1302, 1402: First switching capacitor converters

[0078] 703, 803, 903, 1003, 1103, 1103b, 1203, 1303, 1403: Second switching capacitor converter

[0079] C1, C11, C12, C13, C2, C3: (Non-)resonant capacitors / capacitors

[0080] C21: Upper resonant capacitor

[0081] Cd: Current sensing signal

[0082] CV1, CV2: Non-resonant capacitors

[0083] GA: First Operation Signal

[0084] GB: Second Operation Signal

[0085] I1: First current

[0086] I2: Second current

[0087] IC1: Resonant capacitor current

[0088] IL, IL1, IL11, IL12, IL2, IL3, ILo, ILo1, ILo11, ILo12, ILo2, ILo3: Inductor current

[0089] L, L1, L11, L12, L2, L3: Inductors

[0090] LX: Switch Node

[0091] LX1, LX11: First switching nodes

[0092] LX2, LX12: Second switching nodes

[0093] Q1~Q21, Q28: Switches

[0094] T1, T1', T2, T2': During conduction

[0095] Td1, Td1', Td2, Td2': Delay time

[0096] Tz: Zero current period

[0097] V1: First voltage

[0098] V2: Second voltage

[0099] VC1, VC2, VC3: (Resonant capacitors) Voltage across Detailed Implementation

[0100] The accompanying drawings in this invention are all schematic and are mainly intended to show the coupling relationship between various circuits and the relationship between various signal waveforms. The circuits, signal waveforms and frequencies are not drawn to scale.

[0101] Figure 2A This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to an embodiment of the present invention. Figure 2A As shown, a switching capacitor voltage converter 20 is used to convert a first voltage V1 to a second voltage V2 or vice versa. The switching capacitor voltage converter 20 includes a control circuit 201 and a switching capacitor converter 202. The switching capacitor converter 202 is coupled between the first voltage V1 and the second voltage V2. The control circuit 201 generates a control signal to control the switching capacitor converter 202, thereby converting the first voltage V1 to the second voltage V2 or vice versa. The switching capacitor converter 202 includes at least one resonant capacitor C1, multiple switches (e.g., switches Q1 to Q4), and at least one inductor L. The inductor L is coupled to the at least one resonant capacitor C1. The control circuit 201 generates a control signal, which includes a first operation signal GA and a second operation signal GB. The first operation signal GA is used to operate multiple first switches (e.g., switches Q1 and Q2) of multiple switches (e.g., switches Q1 to Q4), and the second operation signal GB is used to operate multiple second switches (e.g., switches Q3 and Q4) of multiple switches (e.g., switches Q1 to Q4).

[0102] In the first procedure, a first operation signal GA controls the switching of multiple first switches (e.g., switches Q1 and Q2), causing at least one resonant capacitor C1 and its corresponding inductor L to be connected in series between the first voltage V1 and the second voltage V2, forming a first current path and operating resonantly. In at least one second procedure, a second operation signal GB controls the switching of multiple second switches (e.g., switches Q3 and Q4), causing at least one resonant capacitor C1 and its corresponding inductor L to be connected in series between the second voltage V2 and a DC potential, simultaneously or alternately forming multiple second current paths and operating resonantly. In one embodiment, the control circuit 201 adjusts the operating frequency and / or duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, thereby adjusting the ratio between the first voltage V1 and the second voltage V2 to the preset ratio. The first procedure and at least one second procedure are repeatedly and alternately ordered to convert the first voltage V1 to the second voltage V2 or the second voltage V2 to the first voltage V1. In one embodiment, the first voltage V1 is twice the second voltage V2, and the first operating signal GA and the second operating signal GB each have their corresponding operating frequencies. In one embodiment, a preset ratio is the ratio of the first voltage V1 to the second voltage V2, and the operating frequencies of the first operating signal GA and / or the second operating signal GB are positively correlated with this preset ratio. In one embodiment, the operating frequency of the first operating signal GA is higher than the resonant frequency of at least one resonant capacitor C1 and its corresponding inductor L in the first program, and the operating frequency of the second operating signal GB is higher than the resonant frequency of at least one resonant capacitor C1 and its corresponding inductor L in the second program. In one embodiment, the aforementioned DC potential is a ground potential.

[0103] Figure 2B This is a circuit block diagram showing a control circuit for a switching capacitor voltage conversion circuit according to an embodiment of the present invention. Please also refer to... Figure 2A and Figure 2B In one embodiment, the control circuit 201 includes a current sensing circuit 2011 and a control signal generating circuit 2012. The current sensing circuit 2011 is used to sense the current flowing through at least one inductor L to generate at least one current sensing signal Cd, and the control signal generating circuit 2012 is coupled to the current sensing circuit 2011 to generate a control signal based on the current sensing signal Cd and a preset ratio.

[0104] Figure 2C This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to an embodiment of the present invention. Please refer to... Figure 2AWhen the control circuit 201 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, and during the first program and / or the second program, when multiple first switches (e.g., switches Q1 and Q2) and / or multiple second switches (e.g., switches Q3 and Q4) are turned on, the inductor current ILo flowing towards the second voltage V2 is in a first state. In one embodiment, the inductor current ILo flowing towards the second voltage V2 in the first state is a resonant current.

[0105] Please refer to the following: Figure 2C When the control circuit 201 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program and / or the second program, the inductor current IL flowing through the corresponding inductor L continues to flow through a current freewheeling path, thereby causing the inductor current ILo flowing toward the second voltage V2 to be in the second state, so that the corresponding inductor L performs inductive power conversion switching between the first state and the second state.

[0106] The aforementioned current freewheeling path can be implemented in various ways. For example, please refer to [reference needed]. Figure 2C When the control circuit 201 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program and / or the second program, and when multiple first switches (e.g., switches Q1 and Q2) and multiple second switches (e.g., switches Q3 and Q4) are not turned on, the inductor current IL flowing through the corresponding inductor L passes through the body diode (e.g., in at least one switch (e.g., switches Q2 and Q4)) of the internal diode (e.g., in the case of a switch). Figure 2C The conduction of the inductor (shown by the dashed line) allows for freewheeling, which in turn puts the inductor current ILo flowing toward the second voltage V2 in the second state, causing the corresponding inductor L to switch between the first and second states via inductive power supply switching. The freewheeling path includes the non-conducting switch Q2 and the body diode in Q4.

[0107] In another implementation of the current freewheeling path, for example, please refer to... Figure 2C When the control circuit 201 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program and / or the second program, and when switches Q1 and Q3 are not turned on, and switches Q2 and Q4 are both turned on, the inductor current IL flowing through the corresponding inductor L continues to flow through the turned-on switches Q2 and Q4, thereby putting the inductor current ILo flowing towards the second voltage V2 in the second state, so that the corresponding inductor L performs inductive power supply switching between the first state and the second state. The current freewheeling path includes the turned-on switches Q2 and Q4.

[0108] In one embodiment, the inductor current ILo flowing toward the second voltage V2 in the second state is a non-resonant current. In a preferred embodiment, the inductor current ILo in the second state, where the inductor current ILo stops flowing toward the second voltage V2 or the inductor current ILo flowing toward the second voltage V2, is a linear ramp current. In this embodiment, as... Figure 2C As shown, the inductor current ILo flowing toward the second voltage V2 is a linear ramp current.

[0109] In a preferred embodiment, when the control circuit 201 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, and during the first program and / or the second program, when multiple switches (e.g., switches Q1 to Q4) are not turned on, one end of the corresponding inductor L is connected to the body diode (e.g., in at least one switch Q2 and Q4) via an internal diode (e.g., in the case of a switch Q2 and Q4). Figure 2C (As shown by the dashed line) and connected to a DC potential, the inductor current ILo flowing towards the second voltage V2 is a linear ramp current, thereby adjusting the preset ratio. For example, the inductor L is connected in series between the second voltage V2 and the ground potential via the internal diodes in switches Q4 and Q2, so that the inductor current IL flows according to, for example... Figure 2C The current direction indicated by the dashed arrow in the middle continues, making the inductor current ILo flowing toward the second voltage V2 a linear ramp current, in order to adjust the preset ratio.

[0110] Figure 3A This is a schematic diagram of the signal waveforms of a control circuit for a switching capacitor voltage conversion circuit according to an embodiment of the present invention. Figure 3A The diagram shows the first operating signal GA and the second operating signal GB without duty cycle adjustment. The duty cycles of both the first operating signal GA and the second operating signal GB are approximately 50%. Figure 3A As shown, the conduction period T1 of the plurality of first switches (e.g., switches Q1 and Q2) and the conduction period T2 of the plurality of second switches (e.g., switches Q3 and Q4) do not overlap with each other, so that the first procedure and the second procedure do not overlap with each other.

[0111] Figure 3B This is a schematic diagram of the signal waveforms of a control circuit for a switching capacitor voltage conversion circuit according to an embodiment of the present invention. Figure 3B The diagram shows the first operating signal GA and the second operating signal GB after reducing the duty cycle. Figure 3A and Figure 3B As shown, after reducing the duty cycle, the conduction period T1 of multiple first switches (e.g., switches Q1 and Q2) and the conduction period T2 of multiple second switches (e.g., switches Q3 and Q4) are reduced to conduction periods T1' and T2', respectively, and the delay times Td1 and Td2 are increased to delay times Td1' and Td2', respectively.

[0112] Figure 3C This is a schematic diagram of signal waveforms showing relevant signals of a switching capacitor voltage converter circuit according to an embodiment of the present invention. This embodiment shows the signal waveforms without adjusting the duty cycle and operating frequency. The second voltage V2, the second current I2, the inductor current IL, the resonant capacitor voltage VC1, the resonant capacitor current IC1, and the first current I1 are displayed. Figure 3C In this embodiment, the first voltage V1 is 48V and the second voltage V2 is 24V. Figure 3D This is a schematic diagram of signal waveforms for a switching capacitor voltage converter circuit according to another embodiment of the present invention. This embodiment shows the signal waveforms when the duty cycle is reduced but the operating frequency remains unchanged. The second voltage V2, the second current I2, the inductor current IL, the resonant capacitor voltage across VC1, the resonant capacitor current IC1, the first current I1, the first operating signal GA, and the second operating signal GB are displayed. Figure 3D In this embodiment, the first voltage V1 is 48V and the second voltage V2 is 16V. In this embodiment and other embodiments, as... Figure 3D As shown, in the first procedure and / or the second procedure, after the inductor current IL flowing through the corresponding inductor L decreases to 0, multiple switches (e.g., switches Q1 to Q4) remain unconducted for a zero-current period Tz, thereby allowing for further adjustment of the ratio of the first voltage V1 to the second voltage V2.

[0113] Figure 3E This is a schematic diagram of signal waveforms for a switching capacitor voltage converter circuit according to another embodiment of the present invention. This embodiment shows the signal waveforms when the duty cycle is reduced and the operating frequency is increased. The second voltage V2, the second current I2, the inductor current IL, the resonant capacitor voltage across VC1, the resonant capacitor current IC1, the first current I1, the first operating signal GA, and the second operating signal GB are displayed. Figure 3E In this embodiment, the first voltage V1 is 48V and the second voltage V2 is 16V. (The rest of the text appears to be incomplete and requires further context.) Figure 3E It can be seen that the ripple in this embodiment is relatively small. Figure 3D Small.

[0114] Figure 3F This is a schematic diagram of signal waveforms for a switching capacitor voltage converter circuit according to another embodiment of the present invention. This embodiment illustrates the signal waveforms when the duty cycle is reduced and the operating frequency is further increased. The second voltage V2, the second current I2, the inductor current IL, the resonant capacitor voltage across VC1, the resonant capacitor current IC1, the first current I1, the first operating signal GA, and the second operating signal GB are shown in... Figure 3F In this embodiment, the first voltage V1 is 48V and the second voltage V2 is 24V. (The rest of the text appears to be a fragment and requires further context for accurate translation.) Figure 3F It can be seen that the ripple in this embodiment is relatively small. Figure 3E Smaller.

[0115] Figure 4 This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to another embodiment of the present invention. The switching capacitor voltage conversion circuit 30 is used to convert a first voltage V1 to a second voltage V2, or to convert a second voltage V2 to a first voltage V1. In this embodiment, the switching capacitor voltage conversion circuit 30 includes a control circuit 301 and a switching capacitor converter 302. The switching capacitor converter 302 includes a non-resonant capacitor C1, a resonant capacitor C2, a resonant capacitor C3, and a plurality of switches (e.g., switches Q1 to Q10) coupled to each other. It should be noted that when the capacitance value of capacitor C1 is much larger than the capacitance values ​​of capacitors C2 and C3, capacitor C1 can be considered a non-resonant capacitor.

[0116] In one embodiment, in the first procedure, multiple switches (e.g., switches Q1-Q10) control a non-resonant capacitor C1 and a resonant capacitor C3 connected in series between a first voltage V1 and a second voltage V2, and control a resonant capacitor C2 connected in parallel with the second voltage V2. The other end of the resonant capacitor C2 is controlled to be coupled to ground potential. Specifically, switches Q1, Q2, and Q3 are turned on to control the non-resonant capacitor C1 and the resonant capacitor C3 connected in series between the first voltage V1 and the second voltage V2, switches Q4 and Q5 are turned on to control the resonant capacitor C2 connected in parallel with the second voltage V2, and switches Q6-Q10 are not turned on. In this embodiment, in the first procedure, the control signal GA is enabled, making the switch it controls turn on, and the control signal GB is disabled, making the switch it controls turn off.

[0117] In the second procedure, multiple switches (e.g., switches Q1-Q10) control the resonant capacitor C2 and the non-resonant capacitor C1 to be connected in series between the second voltage V2 and the ground potential, and control the resonant capacitor C3 to be connected in parallel with the second voltage V2. In the second procedure, the resonant capacitor C2 and the non-resonant capacitor C1 are connected in reverse series between the second voltage V2 and the ground potential. Specifically, switches Q6, Q7, and Q8 are turned on to control the resonant capacitor C2 and the non-resonant capacitor C1 to be connected in series between the second voltage V2 and the ground potential, and switches Q9 and Q10 are turned on to control the resonant capacitor C3 to be connected in parallel with the second voltage V2, while switches Q1-Q5 are not turned on. In this embodiment, in the second procedure, the control signal GA is disabled, making the switch it controls non-conducting, and the control signal GB is enabled, making the switch it controls conduct.

[0118] The switching capacitor voltage conversion circuit 30 performs power conversion between the first voltage V1 and the second voltage V2 through the aforementioned periodic operation. In this embodiment, the ratio of the first voltage V1 to the second voltage V2 is 4.

[0119] It should be noted that in the second procedure mentioned above, the resonant capacitor C2 and the non-resonant capacitor C1 are connected in series in reverse, which means that the voltage across the resonant capacitor C2 and the voltage across the non-resonant capacitor C1 are out of phase (i.e., the positive and negative terminals are in opposite directions).

[0120] In the embodiment of converting the first voltage V1 to the second voltage V2, in the first process, the first voltage V1 charges the non-resonant capacitor C1 and the resonant capacitor C3 connected in series, while the resonant capacitor C2 discharges to supply the second voltage V2; that is, the resonant capacitor C2 charges the non-resonant capacitor C2 coupled to the second voltage V2. In the second process, the non-resonant capacitor C1 charges the resonant capacitor C2 and the second voltage V2.

[0121] Furthermore, in the embodiment where the second voltage V2 is converted into the first voltage V1, in the first process, the second voltage V2 charges the non-resonant capacitor C1 and the resonant capacitor C3 connected in series, and the second voltage V2 also charges the resonant capacitor C2. In the second process, the second voltage V2 charges the resonant capacitor C3, and the second voltage V2 charges the non-resonant capacitor C1 through the resonant capacitor C2.

[0122] Through the aforementioned periodic operation, in this embodiment, in steady state, the ratio of the voltage across the non-resonant capacitor C1 (VC1) to the second voltage V2 is 2, the ratio of the voltage across the resonant capacitor C3 (VC3) to the second voltage V2 is 1, and the ratio of the voltage across the resonant capacitor C2 (VC2) to the second voltage V2 is 1. In the embodiment where the second voltage V2 is 12V, in steady state, the voltage across the resonant capacitors C3 (VC3) and C2 (VC2) are also both 12V. It is worth noting that, since this invention allows the voltage across the capacitors to remain at a relatively low level in steady state, the capacitors can maintain a high effective capacitance value. Therefore, the required voltage rating and size of the capacitors can be effectively reduced. Simultaneously, the resonant frequency is more stable, and the instantaneous response is better. It is also worth noting that the output current of this invention (e.g., corresponding to the second current I2) is provided by two channels, thus reducing ripple.

[0123] Non-resonant capacitors CV1 and CV2, respectively coupled to the first voltage V1 and the second voltage V2, correspond to the input capacitor and the output capacitor, respectively, in the embodiment where the first voltage V1 is converted to the second voltage V2, or, in the embodiment where the second voltage V2 is converted to the first voltage V1, respectively, to the output capacitor and the input capacitor.

[0124] The switching capacitor converter 302 also includes inductors L1 and L2, wherein inductor L1 is coupled between the second voltage V2 and the first switching node LX1, and inductor L2 is coupled between the second voltage V2 and the second switching node LX2. In the first program, multiple switches (e.g., switches Q1 to Q10) control the non-resonant capacitor C1 and the resonant capacitor C3, which are connected in series with inductor L1 through the first switching node LX1, and then connected in series between the first voltage V1 and the second voltage V2. Furthermore, the resonant capacitor C2 is controlled to be connected in series with inductor L2 through the second switching node LX2, and then connected in parallel with the second voltage V2. On the other hand, in the second program, multiple switches (e.g., switches Q1 to Q10) control the resonant capacitor C2 and the non-resonant capacitor C1, which are connected in series with inductor L2 through the second switching node LX2, and then connected in parallel between the second voltage V2 and the ground potential. Furthermore, the resonant capacitor C3 is controlled to be connected in series with inductor L1 through the first switching node LX1, and then connected in parallel with the second voltage V2. In one embodiment, both inductors L1 and L2 operate in continuous conduction mode, thereby further reducing surge current and ripple current.

[0125] In one embodiment, the capacitance of the non-resonant capacitor C1 is much larger than that of the resonant capacitors C3 and C2, such that the first resonant frequency of the resonant capacitor C3 and the inductor, and the second resonant frequency of the resonant capacitor C2 and the inductor, are both much higher than the third resonant frequency of the non-resonant capacitor C1 and the inductor. In a preferred embodiment, the first resonant frequency and the second resonant frequency are both greater than or equal to 10 times the third resonant frequency.

[0126] The control circuit 301 in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0127] Figure 5 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. In this embodiment, the switching capacitor converter 402 and... Figure 4Similar to the switching capacitor converter 302, the difference lies in that the inductor L1 of the switching capacitor converter 402 is directly connected in series with the resonant capacitor C3 to form a resonant slot 4021, while the inductor L2 of the switching capacitor converter 402 is directly connected in series with the resonant capacitor C2 to form a resonant slot 4022. In one embodiment, in the first process, multiple switches (e.g., switches Q1 to Q10) control the resonant slot 4021 and the non-resonant capacitor C1 to be connected in series between the first voltage V1 and the second voltage V2, and control the resonant slot 4022 to be connected in parallel with the second voltage V2. On the other hand, in the second process, multiple switches (e.g., switches Q1 to Q10) control the resonant slot 4022 and the non-resonant capacitor C1 to be connected in series between the second voltage V2 and the ground potential, and control the resonant slot 4021 to be connected in parallel with the second voltage V2. Through the above periodic operation, the switching capacitor converter 402 operates in a resonant manner to realize the power conversion between the first voltage V1 and the second voltage V2. For control details of the aforementioned switches (e.g., switches Q1 to Q10), please refer to [reference needed]. Figure 4 Examples of implementations.

[0128] The control circuit 401 in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. For example... Figure 5 As shown, when the control circuit 401 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program and / or the second program, and when multiple first switches (e.g., switches Q1 to Q5) and multiple second switches (e.g., switches Q6 to Q10) are not turned on, the inductor currents IL1 and IL2 flowing through the corresponding inductors L1 and L2 respectively pass through the internal diodes (body diodes) in at least one switch (e.g., switches Q9 and Q3 and switches Q4 and Q6). Figure 5 The conduction of the circuit (shown by the dashed line) is achieved through resonant slots 4021 and 4022 and at least one switch (e.g., switches Q9 and Q3 and switches Q4 and Q6) with an internal diode (e.g., ...). Figure 5 The closed loops 4023 and 4024 (shown by the dashed line) form a freewheeling loop, thereby causing the inductor currents ILo1 and ILo2 in the second state to stop flowing towards the second voltage V2. Figure 5 As shown, at least one resonant capacitor C3 and at least one inductor L1 form a resonant tank 4021, and at least one resonant capacitor C2 and at least one inductor L2 form a resonant tank 4022. In this case, the closed-loop current (i.e., the inductor currents IL1 and IL2) has no net current flowing into or out of the non-resonant capacitor (also known as the output capacitor) CV2.

[0129] For example, the inductor current IL1 flowing through the corresponding inductor L1 is turned on by the internal diodes in switches Q9 and Q3, and then freewheels through the closed loop 4023 formed by the resonant tank 4021 and the internal diodes in switches Q9 and Q3, thereby causing the inductor current ILo1 to stop flowing towards the second voltage V2 in the second state. The inductor current IL2 flowing through the corresponding inductor L2 is turned on by the internal diodes in switches Q4 and Q6, and then freewheels through the closed loop 4024 formed by the resonant tank 4022 and the internal diodes in switches Q4 and Q6, thereby causing the inductor current ILo2 to stop flowing towards the second voltage V2 in the second state.

[0130] Figure 6 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. In this embodiment, the switching capacitor converter 502 and... Figure 4 Similar to the switching capacitor converter 302, the difference lies in that the switching capacitor converter 502 shares an inductor L, which is coupled between the second voltage V2 and the switching node LX. In the first process, multiple switches (e.g., switches Q1 to Q10) control the non-resonant capacitor C1 and the resonant capacitor C3, which are connected in series with the inductor L through the switching node LX, and then connected in series between the first voltage V1 and the second voltage V2. Furthermore, the resonant capacitor C2 is controlled to be connected in series with the inductor L through the switching node LX, and then connected in parallel with the second voltage V2. On the other hand, in the second process, multiple switches (e.g., switches Q1 to Q10) control the resonant capacitor C2 and the non-resonant capacitor C1, which are connected in series with the inductor L through the switching node LX, and then connected in parallel with the second voltage V2. In this embodiment, the non-resonant capacitor C1, the resonant capacitor C2, and the resonant capacitor C3 all resonate with the inductor L to switch between the first voltage V1 and the second voltage V2. For control details of the aforementioned switches (e.g., switches Q1 to Q10), please refer to [reference needed]. Figure 4 Examples of implementations.

[0131] The control circuit 501 in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0132] It is worth noting that in this embodiment, the capacitor and the inductor resonate during the charging and discharging process. Therefore, the surge current of the capacitor during charging and discharging can be effectively reduced. Furthermore, zero-current switching control or zero-voltage switching control can be achieved through the characteristics of resonance. The same applies to the embodiments that operate in a resonant manner, which will be described in detail later.

[0133] Figure 7 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 7 The shown switching capacitor converter 402a can correspond to Figure 5 Specifically, in this embodiment, in the 2x conversion mode, switch Q1 of the capacitor switching converter 402a is always on (shown as a short circuit), while switches Q2, Q3, and Q8-Q10 are always off. Switches Q4-Q7 are used to switch the resonant capacitor C2. In the first program, the resonant capacitor C2 and inductor L2 are connected in series between the first voltage V1 and the second voltage V2. In the second program, the resonant capacitor C2 and inductor L2 are connected in series and then in parallel to the second voltage V2, making the ratio of the first voltage V1 to the second voltage V2 2. The resonant capacitor C2 and inductor L2 operate in a resonant manner to achieve power conversion between the first voltage V1 and the second voltage V2. In this embodiment, since switches Q2, Q3, and Q8-Q10 are always off, at least one end of the resonant slot 4021a (resonant capacitor C3, inductor L1) and the non-resonant capacitor C1 are also always floating.

[0134] The control circuit 401a in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 5 Please refer to the information about Figure 5 A detailed description.

[0135] Figure 8 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 8 The shown capacitor switching converter 502a can correspond to Figure 6Specifically, in this embodiment, in the 2x conversion mode, switch Q1 of the switching capacitor converter 502a is always on (shown as a short circuit), while switches Q2, Q3, and Q8-Q10 are always off. Switches Q4-Q7 are used to switch the resonant capacitor C2. In the first program, the resonant capacitor C2 is connected in series with the inductor L through the switching node LX before being connected in series between the first voltage V1 and the second voltage V2. In the second program, the resonant capacitor C2 is connected in series with the inductor L through the switching node LX and then connected in parallel with the second voltage V2. In other words, in the second program, switches Q4-Q7 control the resonant capacitor C2 to be connected in series with the inductor L through the switching node LX between the second voltage V2 and the ground potential, so that the ratio of the first voltage V1 to the second voltage V2 is 2. The resonant capacitor C2 and the inductor L operate in a resonant manner to realize the power conversion between the first voltage V1 and the second voltage V2. In this embodiment, since switches Q2, Q3, and Q8 to Q10 are always not conducting, at least one end of each of the non-resonant capacitor C1 and the resonant capacitor C3 is always floating.

[0136] The control circuit 501a in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0137] Figure 9 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 9 The shown switching capacitor converter 302a can correspond to Figure 4Specifically, in this embodiment, in the 2x conversion mode, switches Q4 and Q9 of the capacitor switching converter 302a are always on (shown as short circuits), while switches Q3, Q5, Q6, and Q10 are always off. Switches Q1, Q2, Q7, and Q8 are used to switch the resonant capacitor C1. In the first program, the resonant capacitor C1 is controlled to be connected in series with inductor L1 through the first switching node LX1 before being connected in series between the first voltage V1 and the second voltage V2. In the second program, the resonant capacitor C1 is controlled to be connected in series with inductor L2 through the second switching node LX2 before being connected in parallel with the second voltage V2. It should be noted that since this embodiment makes some switches Q4 and Q9 always on and some switches Q3, Q5, Q6, and Q10 always off, the effective circuit only contains capacitor C1. Therefore, capacitor C1 in this embodiment should be regarded as the resonant capacitor. In other words, in the second program, switches Q1, Q2, Q7, and Q8 control the resonant capacitor C1 to be connected in series with inductor L2 through the second switching node LX2 between the second voltage V2 and the ground potential, making the ratio of the first voltage V1 to the second voltage V2 2. The resonant capacitor C1, along with inductors L1 and L2, operates in a resonant manner to achieve the power conversion between the first voltage V1 and the second voltage V2. In this embodiment, since switches Q3, Q5, Q6, and Q10 are always non-conducting, at least one end of each of the resonant capacitors C3 and C2 is also always floating.

[0138] The control circuit 301a in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0139] Figure 10 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 10 The shown capacitor switching converter 502b can correspond to Figure 6Specifically, in this embodiment, in the 3x conversion mode, switch Q4 of the capacitor switching converter 502b is always on (shown as a short circuit), while switches Q5 and Q6 are always off. Switches Q1-Q3 and Q7-Q10 are used to switch between non-resonant capacitor C1 and resonant capacitor C3. In the first program, non-resonant capacitor C1 and resonant capacitor C3 are connected in series with inductor L between the first voltage V1 and the second voltage V2. In the second program, non-resonant capacitor C1 and resonant capacitor C3 are connected in parallel, then in series with inductor L, and finally in parallel with the second voltage V2, so that the ratio of the first voltage V1 to the second voltage V2 is 3. The non-resonant capacitor C1 and resonant capacitor C3 and inductor L operate in a resonant manner to achieve power conversion between the first voltage V1 and the second voltage V2. In this embodiment, since switches Q5 and Q6 are always off, one end of resonant capacitor C2 is also always floating.

[0140] The control circuit 501b in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0141] Figure 11 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 11 The shown switching capacitor converter 302b can correspond to Figure 4 The switching capacitor converter 302 operates similarly to the switching capacitor converter 502b, except that in the first program, the non-resonant capacitor C1, resonant capacitor C3, and inductor L1 of the switching capacitor converter 302b are connected in series between the first voltage V1 and the second voltage V2. In the second program, the resonant capacitor C3 and the non-resonant capacitor C1 are connected in series with inductors L1 and L2 respectively, and then connected in parallel with the second voltage V2, resulting in a ratio of 3 between the first voltage V1 and the second voltage V2. Details of the switch operation can be found in [reference needed]. Figure 10 Examples of implementations.

[0142] The control circuit 301b in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0143] It should be noted that the above Figures 7-11, respectively corresponding to the aforementioned Figure 5 , Figure 6 , Figure 4 The switch and component configuration allows for several different ratios to be set between the first voltage V1 and the second voltage V2. This is achieved by having some switches constantly on, others constantly off, and the remaining switches switching according to the desired mode. Furthermore, Figures 7-11 This is to show the aforementioned Figure 5 , Figure 6 , Figure 4 The equivalent circuit diagram of the embodiment is shown, in which the switch that is always non-conducting and the capacitor that is always floating are omitted in the figure to simplify the drawing.

[0144] Figure 12 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 12 The switching capacitor converter 602 shown is similar to Figure 4 In the switching capacitor converter 302 shown in this embodiment, the inductors L1 and L2 of the switching capacitor converter 602 are mutually inductive. Therefore, the inductor currents IL1 and IL2 of the switching capacitor converter 602 can have a better current balance. At the same time, the resonant capacitors C3 and C2 can also have a better voltage balance.

[0145] The control circuit 601 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0146] In one embodiment, inductors L1 and L2 may be configured as coupled inductors or as a transformer (such as transformer 6021).

[0147] Figure 13 This is a circuit diagram illustrating a switching capacitor voltage converter circuit according to another embodiment of the present invention. In one embodiment, the switching capacitor voltage converter circuit 70 includes a first switching capacitor converter 702 and a second switching capacitor converter 703, which are connected in parallel and coupled between the first voltage V1 and the second voltage V2. In this embodiment, the first switching capacitor converter 702 and the second switching capacitor converter 703 correspond, for example, to the aforementioned... Figure 5In this embodiment, the switching capacitor converter 402, by operating multiple switching capacitor converters in parallel, can increase the output power or reduce the ripple current. It should be noted that "parallel operation" of the switching capacitor converters means that the input terminals of the switching capacitor converters are electrically connected to each other, for example, a first voltage V1, and the output terminals of the switching capacitor converters are electrically connected to each other, for example, a second voltage V2.

[0148] In one embodiment, the first switching capacitor converter 702 and the second switching capacitor converter 703 switch the corresponding plurality of switches in each switching capacitor converter with opposite phases to each other, performing power conversion in an interleaved manner. Specifically, as shown in the example... Figure 13 As shown, the control signals GA and GB of the switches Q1 to Q10 of the first switching capacitor converter 702 are... Figure 5 The switching capacitor converter 402 is in phase, while the control signals GA and GB of the switches Q11 to Q20 of the second switching capacitor converter 703 are in phase. Figure 5 The switching capacitor converter 402 is inverted (and therefore also inverted with the first switching capacitor converter 702).

[0149] The first switching capacitor converter 702 and the second switching capacitor converter 703 include inductors L1, L2, L11, and L12, which are connected in series with resonant capacitors C3, C2, C13, and C12 to form resonant slots 7021, 7022, 7031, and 7032, respectively. This embodiment uses an interleaved operation of the first switching capacitor converter 702 and the second switching capacitor converter 703 to perform power conversion, and the first switching capacitor converter 702 and the second switching capacitor converter 703 are each similar to those described above. Figure 5 The switching capacitor converter 402 in the middle performs power conversion in a resonant manner.

[0150] The control circuit 701 in this embodiment can be adopted. Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 5 Please refer to the information about Figure 5 A detailed description.

[0151] Figure 14 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 14 Switching capacitor voltage conversion circuit 80 and Figure 13Similar to the switching capacitor voltage converter circuit 70, the switching capacitor voltage converter circuit 80 includes a first switching capacitor converter 802 and a second switching capacitor converter 803. The difference is that the first switching capacitor converter 802 shares inductor L1, while the second switching capacitor converter 803 shares inductor L11, and so on. Figure 6 In this embodiment, the resonant capacitors C3 and C2 are connected in parallel and then in series with the inductor L1, similar to... Figure 6 In this embodiment, the resonant capacitors C13 and C12 are connected in parallel and then in series with the inductor L11. (Similar to...) Figure 13 The switching capacitor voltage converter circuit 70 in this embodiment also performs power conversion by interleaving the first switching capacitor converter 802 and the second switching capacitor converter 803. The first switching capacitor converter 802 and the second switching capacitor converter 803 are each similar to those described above. Figure 6 The switching capacitor converter 502 in the middle performs power conversion in a resonant manner.

[0152] The control circuit 801 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0153] Figure 15 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 15 Switching capacitor voltage conversion circuit 90 and Figure 13 Similar to the switching capacitor voltage converter circuit 70, the switching capacitor voltage converter circuit 90 includes a first switching capacitor converter 902 and a second switching capacitor converter 903. The difference is that the inductors L1, L2, L11, and L12 of the first switching capacitor converter 902 and the second switching capacitor converter 903 are not directly connected in series with the resonant capacitors C3, C2, C13, and C12, respectively. Instead, they are connected in series with the resonant capacitors C3, C2, C13, and C12 through the first switching node LX1, the second switching node LX2, the first switching node LX11, and the second switching node LX12, respectively. As... Figure 13 The switching capacitor voltage conversion circuit 70 in this embodiment also performs power conversion by interleaving the first switching capacitor converter 902 and the second switching capacitor converter 903. The first switching capacitor converter 902 and the second switching capacitor converter 903 are each similar to those described above. Figure 4 The switching capacitor converter 302 in the middle performs power conversion in a resonant manner.

[0154] The control circuit 901 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0155] Figure 16 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 16 Switching capacitor voltage conversion circuit 100 and Figure 15 Similar to the switching capacitor voltage converter circuit 90, the inductors L1, L2, L11, and L12 in the switching capacitor voltage converter circuit 100 are mutually inductive. Therefore, the inductor currents IL1, IL2, IL11, and IL12 in the switching capacitor voltage converter circuit 100 can have better current balance, and at the same time, the resonant capacitors C3, C2, C13, and C12 can also have better voltage balance. In one embodiment, the switching capacitor voltage converter circuit 100 can be configured such that all inductors L1, L2, L11, and L12 are mutually inductive, or only some of the inductors are mutually inductive, depending on the requirements. In one embodiment, the inductors L1, L2, L11, and L12 can be configured as at least one transformer.

[0156] The control circuit 1001 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0157] Figure 17 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 17 The shown switching capacitor voltage converter circuit 110 includes a first switching capacitor converter 1102 and a second switching capacitor converter 1103, an upper-level resonant capacitor C21, and multiple upper-level switches (e.g., switches Q21, Q28). The first switching capacitor converter 1102 and the second switching capacitor converter 1103 can, for example, correspond to... Figure 5 The switching capacitor converter 402. From one perspective, Figure 17 The switching capacitor voltage converter circuit 110 shown refers to, for example, Figure 5The switching capacitor converter 402 is configured as a multi-layered switching capacitor voltage conversion circuit. Specifically, the upper resonant capacitor C21, multiple upper switches (switches Q21, Q28), the first switching capacitor converter 1102, and the second switching capacitor converter 1103 are coupled to each other in a basic topology. Please also refer to [reference needed]. Figure 18 In one embodiment, the “basic topology” refers to the basic coupling relationship between the upper resonant capacitor C21, multiple upper switches (e.g., switches Q21, Q28), the first switching capacitor converter 1102, and the second switching capacitor converter 1103, which will be described in detail later.

[0158] The control circuit 1101 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 5 Please refer to the information about Figure 5 A detailed description.

[0159] In one embodiment, according to the aforementioned basic topology, the first switching capacitor converter 1102 (corresponding to the first switching capacitor converter 1102b, Figure 18 The input terminal of the capacitor is electrically connected to one end of the upper resonant capacitor C21, and the second switching capacitor converter 1103 (corresponding to the second switching capacitor converter 1103b) is also electrically connected to the input terminal of the capacitor. Figure 18 The input terminal of the first switching capacitor converter 1102 and the output terminal of the second switching capacitor converter 1103 are electrically connected to each other and the second voltage V2.

[0160] In the first procedure (e.g., when the control signal GA is disabled and the control signal GB is enabled), multiple upper-level switches (e.g., switches Q21, Q28) and multiple switches of the first switching capacitor converter 1102 (e.g., switches Q11 to Q20) control the upper-level resonant capacitor C21 to be connected in series with the first switching capacitor converter 1102 and establish at least one current path between the first voltage V1 and the second voltage V2. In addition, multiple upper-level switches (e.g., switches Q21, Q28) and multiple switches of the second switching capacitor converter 1103 (e.g., switches Q1 to Q10) control the upper-level resonant capacitor C21 to be disconnected from the second switching capacitor converter 1103 and control the second switching capacitor converter 1103 to establish at least one current path between the second voltage V2 and the ground potential.

[0161] On the other hand, in the second procedure (for example, when the control signal GA is enabled and the control signal GB is disabled), multiple upper-level switches (switches Q21, Q28) and multiple switches of the second switching capacitor converter 1103 (e.g., switches Q1 to Q10) control the second switching capacitor converter 1103 and the upper-level resonant capacitor C21 to be connected in series between the second voltage V2 and the ground potential, and establish at least one current path between the second voltage V2 and the ground potential. In addition, multiple upper-level switches (switches Q21, Q28) and multiple switches of the first switching capacitor converter 1102 (e.g., switches Q11 to Q20) control the upper-level resonant capacitor C21 and the first switching capacitor converter 1102 to be disconnected, and control the first switching capacitor converter 1102 to establish at least one current path between the second voltage V2 and the ground potential.

[0162] The aforementioned current path is, for example, the current path established by the corresponding switch that is turned on when the control signal GA is enabled or the control signal GB is enabled.

[0163] The first switching capacitor converter 1102 and the second switching capacitor converter 1103 are also configured with, for example Figure 5 The resonant slots in the embodiment, namely resonant slots 11021, 11022, 11031, and 11032, are used to switch between the first voltage V1 and the second voltage V2 in a resonant manner.

[0164] In this embodiment, as Figure 17 The ratio of the first voltage V1 to the second voltage V2 shown is 8. Specifically, in steady state, the voltage across the upper resonant capacitor C21 is 4*V2, the voltage across the non-resonant capacitors C1 and C11 (both corresponding to the non-resonant capacitors in the aforementioned embodiments) is 2*V2, and the voltage across the resonant capacitors C3, C13 (both corresponding to the resonant capacitors in the aforementioned embodiments), and resonant capacitors C2 and C12 (both corresponding to the resonant capacitors in the aforementioned embodiments) is V2.

[0165] Continue reading Figure 18 According to the present invention, it can be achieved through Figure 18 Based on the basic topology, the number of layers in the pipelined switching capacitor voltage converter circuit is recursively expanded to achieve a higher conversion rate between the first voltage V1 and the second voltage V2. For example... Figure 18 As shown, any one of them has the following characteristics Figure 18The basic topology of the pipelined switching capacitor voltage converter circuit can be used to replace the first switching capacitor converter 1102 and the second switching capacitor converter 1103 (for example, the first switching capacitor converter 1102b and the second switching capacitor converter 1103b in the figure can correspond to an N-layer pipelined switching capacitor voltage converter circuit, where N is an integer greater than or equal to 2), thereby obtaining a higher-layer pipelined switching capacitor voltage converter circuit, that is, the pipelined switching capacitor voltage converter circuit 110b will become an N+1-layer pipelined switching capacitor voltage converter circuit.

[0166] For specific examples, such as Figure 17 The pipeline switching capacitor voltage converter circuit 110, substituted into Figure 18 The first switching capacitor converter 1102b and the second switching capacitor converter 1103b, then Figure 18 The pipelined switching capacitor voltage converter circuit 110b will be configured as a 16:1 pipelined switching capacitor voltage converter circuit, and the same substitution configuration can be repeatedly increased to increase the number of layers, thereby continuously increasing the power conversion factor.

[0167] In this embodiment (16:1 switching capacitor voltage conversion circuit), such as Figure 17 The first switching capacitor converter 1102 and the second switching capacitor converter 1103 can be regarded as the lowest level (1st layer) pipeline switching capacitor voltage conversion circuit, and their structure corresponds to the following: Figure 5 The switching capacitor converter 402, and Figure 17 The pipeline-type switching capacitor voltage converter circuit 110 can be regarded as a two-layer pipeline-type switching capacitor voltage converter circuit. Furthermore, with Figure 17 Substituting the 2-layer pipeline switching capacitor voltage converter circuit 110 Figure 18 The first switching capacitor converter 1102b and the second switching capacitor converter 1103b, then Figure 18 The pipeline-type switching capacitor voltage converter circuit 110b shown can be regarded as a 3-layer pipeline-type switching capacitor voltage converter circuit.

[0168] Figure 19 This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 19 The switching capacitor voltage converter circuit 120 shown is similar to Figure 17 The difference between the shown switching capacitor voltage converter circuit 110 and the one shown is that the first switching capacitor converter 1202 shares inductor L11, while the second switching capacitor converter 1203 shares inductor L1, and is similar to... Figure 6 In this embodiment, the resonant capacitors C3 and C2 are connected in parallel and then in series with the inductor L1, similar to... Figure 6In this embodiment, the resonant capacitors C13 and C12 are connected in parallel and then in series with the inductor L11. (Similar to...) Figure 17 The switching capacitor voltage converter circuit 110 in this embodiment also performs power conversion by interleaving the first switching capacitor converter 1202 and the second switching capacitor converter 1203. The first switching capacitor converter 1202 and the second switching capacitor converter 1203 are each similar to those described above. Figure 6 The switching capacitor converter 502 in the middle performs power conversion in a resonant manner.

[0169] The control circuit 1201 in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0170] Figure 20 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 20 The switching capacitor voltage converter circuit 130 shown is similar to Figure 17 The difference between the switching capacitor voltage converter circuit 110 shown is that the inductors L1, L2, L11, and L12 of the first switching capacitor converter 1302 and the second switching capacitor converter 1303 are not directly connected in series with the resonant capacitors C3, C2, C13, and C12, respectively. Instead, they are connected in series with the resonant capacitors C3, C2, C13, and C12 through the first switching node LX1, the second switching node LX2, the first switching node LX11, and the second switching node LX12, respectively. In other words, the switching capacitor voltage converter circuit 130 performs a switching operation in a manner similar to that of the switching capacitor voltage converter circuit 110, and then, through the inductors L1, L2, L11, and L12 and the corresponding resonant capacitors, in a manner similar to that of the switching capacitor voltage converter circuit 110. Figure 4 The resonant mode of the embodiment performs the conversion between the first voltage V1 and the second voltage V2. In this embodiment, the ratio of the first voltage V1 to the second voltage V2 is also 8.

[0171] The control circuit 1301 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0172] Figure 21This is a circuit diagram of a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 21 Switching capacitor voltage conversion circuit 140 and Figure 20 Similar to the switching capacitor voltage converter circuit 130, the inductors L1, L2, L11, and L12 in the switching capacitor voltage converter circuit 140 are mutually inductive. Therefore, the inductor currents IL1, IL2, IL11, and IL12 in the switching capacitor voltage converter circuit 140 can have better current balance, and at the same time, the resonant capacitors C3, C2, C13, and C12 can also have better voltage balance. In one embodiment, the switching capacitor voltage converter circuit 140 can be configured such that all inductors L1, L2, L11, and L12 are mutually inductive, or only some of the inductors are mutually inductive, depending on the requirements. In one embodiment, the inductors L1, L2, L11, and L12 can be configured as at least one transformer.

[0173] The control circuit 1401 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0174] Figure 22A This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to yet another embodiment of the present invention. Figure 22A As shown, the switching capacitor voltage conversion circuit 150 includes resonant capacitors C1 and C3, at least one non-resonant capacitor C2, switches Q1, Q2, Q3, Q4, Q5, Q6, Q7, Q8, Q9, Q10, resonant inductors L1 and L2, and control circuit 1501.

[0175] like Figure 22AAs shown, the control circuit 1501 generates a first operation signal GA and a second operation signal GB to correspond to a first resonant program and a second resonant program, respectively, and operates a plurality of corresponding switches (e.g., switches Q1 to Q10) to switch the electrical connection relationship of the corresponding resonant capacitors C1 and C3 and the non-resonant capacitor C2. The switching capacitor voltage conversion circuit 150 includes at least one resonant slot, such as resonant slots 1502 and 1503. Resonant slot 1502 has a resonant capacitor C1 and a resonant inductor L1 connected in series, while resonant slot 1503 has a resonant capacitor C3 and a resonant inductor L2 connected in series. Switches Q1-Q10 are correspondingly coupled to at least one resonant slot 1502 and 1503, and switch the electrical connection relationship of the corresponding resonant slots 1502 and 1503 according to the corresponding first operation signal GA and second operation signal GB, respectively, to correspond to the first resonant program and the second resonant program. In the first resonance program, the corresponding resonant slots 1502 and 1503 are resonantly charged, and in the second resonance program, the corresponding resonant slots 1502 and 1503 are resonantly discharged. At least one non-resonant capacitor C2 is coupled to at least one resonant slot 1502 or 1503. A first operating signal GA and a second operating signal GB switch the electrical connection between the non-resonant capacitor C2 and the at least one resonant slot 1502 or 1503. The voltage across the non-resonant capacitor C2 is maintained at a fixed ratio to the first voltage V1, for example, half of the first voltage V1 in this embodiment. The first and second resonance programs are repeatedly and alternately sequenced to convert the first voltage V1 to the second voltage V2 or vice versa. The first operating signal GA and the second operating signal GB each switch to a conduction level for a specific conduction period, and these multiple conduction periods do not overlap, ensuring that the first and second resonance programs do not overlap.

[0176] In the first resonance procedure, according to the first operation signal GA, switches Q1, Q3, Q5, Q8, and Q9 are turned on, while switches Q2, Q4, Q6, Q7, and Q10 are turned off. This causes the resonant capacitor C1 and resonant inductor L1 of the resonant tank 1502 to be connected in series between the first voltage V1 and the second voltage V2, and causes the non-resonant capacitor C2, the resonant capacitor C3 of the resonant tank 1503, and the resonant inductor L2 to be connected in series between the ground potential and the second voltage V2. This charges the resonant capacitors C1 and C3 and discharges the non-resonant capacitor C2. In the second resonance procedure, according to the second operation signal GB, switches Q2, Q4, Q6, Q7, and Q10 are turned on, while switches Q1, Q3, Q5, Q8, and Q9 are turned off. This causes the non-resonant capacitor C2, the resonant capacitor C1 of the resonant tank 1502, and the resonant inductor L1 to be connected in series between the ground potential and the second voltage V2. Additionally, the resonant capacitor C3 of the resonant tank 1503 and the resonant inductor L2 are connected in series between the ground potential and the second voltage V2. This discharges the resonant capacitors C1 and C3 and charges the non-resonant capacitor C2.

[0177] Regarding having as Figure 22A and 22B The operation of the switching capacitor voltage conversion circuit 150 of the resonant slots 1502 and 1503 shown is well known to those skilled in the art and will not be described in detail here.

[0178] The control circuit 1501 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. For example... Figure 22A As shown, when the control circuit 1501 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program, and when multiple switches (e.g., switches Q1 to Q10) are not turned on, one end of the corresponding inductor L1 is connected to the internal diode (body diode) in at least one switch (e.g., switches Q8 and Q2). Figure 22A (As shown by the dashed line) and connected to a DC potential, the inductor current ILo1 flowing towards the second voltage V2 is a linear ramp current to adjust the preset ratio. For example, the inductor L1 is connected in series between the second voltage V2 and the ground potential via the internal diodes in switches Q8, Q2, and Q5, so that the inductor current IL1 flows according to, for example... Figure 22A The dashed arrow indicates the direction of the freewheeling current; adjust this preset ratio accordingly. Please refer to [further details]. Figure 22A When the control circuit 1501 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program, and when multiple switches (e.g., switches Q1 to Q10) are not turned on, the inductor current IL2 flowing through the corresponding inductor L2 passes through the body diode (e.g., in at least one switch) (e.g., switches Q4 and Q9). Figure 22A The conduction of the resonant groove 15022 and the internal diode in at least one switch (e.g., switches Q4 and Q9) is achieved through the resonant groove 15022. Figure 22A The closed loop 15023 formed by the dashed line (shown in the middle) allows the inductor current ILo2 to stop flowing towards the second voltage V2 in the second state. In this case, there is no net current flowing into or out of the non-resonant capacitor (also known as the output capacitor) CV2 of the closed loop current (i.e., the inductor current IL2).

[0179] Please refer to the following: Figure 22BWhen the control circuit 1501 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the second program, and when multiple switches (e.g., switches Q1 to Q10) are not turned on, one end of the corresponding inductor L2 is connected to the body diode (e.g., in at least one switch Q10) via an internal diode (body diode). Figure 22B (As shown by the dashed line) and is connected to a DC potential to adjust the preset ratio. For example, inductor L2 is connected in series between the second voltage V2 and the ground potential via the internal diodes in switches Q10, Q3, and Q7, so that the inductor current IL2 is adjusted according to, for example... Figure 22B The current continues in the direction indicated by the dashed arrow in the middle to adjust the preset ratio.

[0180] Figure 23 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 23 As shown, the switching capacitor voltage conversion circuit 160 of the present invention includes resonant capacitors C1-C3, switches Q1-Q10, and inductors L1-L3. Switches Q1-Q3 are connected in series with their corresponding resonant capacitors C1-C3, and resonant capacitors C1-C3 are connected in series with their corresponding inductors L1-L3. It should be noted that the number of capacitors in the power conversion circuit of the present invention is not limited to three in this embodiment, but may also be two or four or more, and the number of inductors is not limited to three in this embodiment, but may also be two or four or more.

[0181] Switches Q1-Q10 can switch the electrical connection between corresponding resonant capacitors C1-C3 and inductors L1-L3 according to the corresponding operating signals. In the first program, switches Q1-Q4 are on and switches Q5-Q10 are off, so that resonant capacitors C1-C3 and inductors L1-L3 are connected in series between the first voltage V1 and the second voltage V2 to form a first current path for charging. In the second program, inductors L1-L3 can be used as discharge inductors. Switches Q5-Q10 are on and switches Q1-Q4 are off, so that resonant capacitor C1 and its corresponding inductor L1 are connected in series between the second voltage V2 and the ground potential, resonant capacitor C2 and its corresponding inductor L2 are connected in series between the second voltage V2 and the ground potential, and resonant capacitor C3 and its corresponding inductor L3 are connected in series between the second voltage V2 and the ground potential, thus forming multiple second current paths for discharging. It should be noted that the first and second procedures described above are performed alternately at different time intervals, rather than simultaneously, to convert the first voltage V1 to the second voltage V2 or the second voltage V2 to the first voltage V1. Specifically, the first and second procedures are repeatedly and alternately ordered to convert the first voltage V1 to the second voltage V2 or the second voltage V2 to the first voltage V1. In this embodiment, the DC bias voltage of each resonant capacitor C1, C2, and C3 is the second voltage V2. Therefore, the resonant capacitors C1, C2, and C3 in this embodiment need to withstand a lower rated voltage, thus allowing the use of smaller capacitors.

[0182] The control circuit 1601 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. For example... Figure 23 As shown, when the control circuit 1601 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program and / or the second program, and when multiple switches (e.g., switches Q1 to Q10) are not turned on, one end of the corresponding inductors L2 and L3 is respectively connected to the body diode (e.g., in at least one switch) through the internal diode (body diode) in at least one switch (e.g., switches Q8 and Q2 and switches Q9 and Q3). Figure 23 (As shown by the dashed line) is connected to a DC potential, so that the inductor currents ILo2 and ILo3 flowing toward the second voltage V2 are linear ramp currents, thereby adjusting the preset ratio. For example, inductor L2 is connected in series between the second voltage V2 and the ground potential via internal diodes in switches Q8, Q2, Q3, and Q4, while inductor L3 is connected in series between the second voltage V2 and the ground potential via internal diodes in switches Q9, Q3, and Q4, so that the inductor currents IL2 and IL3 are respectively connected according to, for example... Figure 23 The current continues in the direction indicated by the dashed arrow in the middle to adjust the preset ratio.

[0183] In one embodiment, the first program has a first resonant frequency, and the second program has a second resonant frequency. In a preferred embodiment, the first resonant frequency and the second resonant frequency are the same.

[0184] In one embodiment, the voltage conversion ratio between the first voltage V1 and the second voltage V2 of the aforementioned switching capacitor voltage conversion circuit 160 can be 4:1, 3:1, or 2:1. It should be noted that this embodiment is a 4:1 power conversion circuit; however, by controlling whether switches Q1-Q10 are on or off, the power conversion circuit of this embodiment can be changed to a 3:1 power conversion circuit. For example, by keeping switch Q7 constantly on and keeping switches Q4 and Q10 constantly off, it can be changed to a 3:1 power conversion circuit. The same method applies to changing it to a 2:1 power conversion circuit.

[0185] Figure 24 This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to another embodiment of the present invention. This embodiment differs from the previous embodiment in that multiple resonant capacitors share a charging inductor or a discharging inductor. Therefore, regardless of the number of resonant capacitors, only one charging inductor and one discharging inductor are needed, further reducing the number of inductors. Figure 24 As shown, the switching capacitor voltage conversion circuit 170 of the present invention includes resonant capacitors C1-C3, switches Q1-Q10, and inductors L1-L2. Switches Q1-Q3 are connected in series with their corresponding resonant capacitors C1-C3, while switch Q4 is connected in series with inductor L1. It should be noted that the number of capacitors in the switching capacitor voltage conversion circuit of the present invention is not limited to three in this embodiment, but may also be two or four or more.

[0186] Switches Q1-Q10 can switch the electrical connection between the corresponding resonant capacitors C1-C3 and inductors L1 and L2 according to the corresponding operation signals. In the first program, according to the first operation signal GA, switches Q1-Q4 are turned on and switches Q5-Q10 are turned off, so that the resonant capacitors C1-C3 are connected in series with each other and then connected in series with inductor L1 between the first voltage V1 and the second voltage V2, forming a first current path for charging. In the second program, according to the second operation signal GB, switches Q5-Q10 are turned on and switches Q1-Q4 are turned off, so that the resonant capacitors C1-C3 are connected in parallel with each other and then connected in series with inductor L2 between the second voltage V2 and the ground potential, forming multiple second current paths for discharging. It should be noted that the first program and the second program are performed alternately at different time periods, rather than simultaneously, to convert the first voltage V1 to the second voltage V2 or the second voltage V2 to the first voltage V1. In this embodiment, the DC bias voltage of each resonant capacitor C1, C2, and C3 is the second voltage V2. Therefore, the resonant capacitors C1, C2, and C3 in this embodiment need to withstand a lower rated voltage, so smaller capacitors can be used.

[0187] The control circuit 1701 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0188] In one embodiment, the first process has a first resonant frequency, and the second process has a second resonant frequency. In a preferred embodiment, the first resonant frequency and the second resonant frequency are the same. In another embodiment, the first resonant frequency and the second resonant frequency are different. In one embodiment, the inductance value of inductor L1 is equal to the inductance value of inductor L2. In another embodiment, the inductance value of inductor L1 is different from the inductance value of inductor L2.

[0189] Figure 25 This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to another embodiment of the present invention. In this embodiment, the charging inductor and the discharging inductor can be the same inductor L, which further reduces the number of inductors. Figure 25As shown, the switching capacitor voltage conversion circuit 180 of the present invention includes resonant capacitors C1-C3, switches Q1-Q10, and inductor L. Switches Q1-Q3 are connected in series with their corresponding resonant capacitors C1-C3, while switch Q4 is connected in series with inductor L. It should be noted that the number of capacitors in the switching capacitor voltage conversion circuit of the present invention is not limited to three in this embodiment, but may also be two or four or more.

[0190] It should be noted that in this embodiment, the charging inductor and the discharging inductor are a single identical inductor L. In the second program, by switching switches Q1-Q10, the resonant capacitors C1-C3 are connected in parallel and then in series with a single identical inductor L. The phrase "the charging inductor and the discharging inductor are a single identical inductor L" means that in the first program (also called the charging program) and the second program (also called the discharging program), the inductor current IL in both the charging and discharging programs flows only through a single inductor L and does not flow through any other inductor components.

[0191] Switches Q1-Q10 can switch the electrical connection between the corresponding resonant capacitors C1-C3 and the inductor L according to the corresponding operation signal. In the first program, according to the first operation signal GA, switches Q1-Q4 are turned on and switches Q5-Q10 are turned off, so that the resonant capacitors C1-C3 are connected in series with each other and then connected in series with the inductor L between the first voltage V1 and the second voltage V2, forming a first current path for charging. In the second program, according to the second operation signal GB, switches Q5-Q10 are turned on and switches Q1-Q4 are turned off, so that the resonant capacitors C1-C3 are connected in parallel with each other and then connected in series with the inductor L between the second voltage V2 and the ground potential, forming multiple second current paths for discharging. It should be noted that the first program and the second program are repeatedly alternated at different time periods, rather than simultaneously, to convert the first voltage V1 to the second voltage V2 or the second voltage V2 to the first voltage V1. In this embodiment, the DC bias voltage of each resonant capacitor C1 to C3 is the second voltage V2. Therefore, the resonant capacitors C1 to C3 in this embodiment need to withstand a lower rated voltage, so smaller capacitors can be used.

[0192] The control circuit 1801 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0193] In one embodiment, the voltage conversion ratio of the first voltage V1 to the second voltage V2 of the switching capacitor voltage conversion circuit 180 can be 4:1, 3:1 or 2:1.

[0194] In one embodiment, the voltage conversion ratio of the switching capacitor voltage conversion circuit 180 can be flexibly adjusted. For example, in the first and second programs, by selecting to keep switch Q7 constantly on and selecting to keep switches Q10 and Q4 constantly off, the voltage conversion ratio of the switching capacitor voltage conversion circuit 180 can be adjusted to 3:1. Similarly, for example, by selecting to keep switch Q6 constantly on and selecting to keep switches Q9, Q3, Q7, Q10, and Q4 constantly off, the voltage conversion ratio of the switching capacitor voltage conversion circuit 180 can be adjusted to 2:1.

[0195] Figure 26 This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to yet another embodiment of the present invention. Figure 26 As shown, the switching capacitor voltage conversion circuit 190 of the present invention includes resonant capacitors C1 to C2, switches Q1 to Q7, and inductor L. Switches Q1-Q2 are connected in series with their corresponding resonant capacitors C1-C2, while switch Q3 is connected in series with inductor L.

[0196] Switches Q1-Q7 can switch the electrical connection between the corresponding resonant capacitors C1-C2 and the inductor L according to the corresponding operation signals. In the first program, according to the first operation signal GA, switches Q1-Q3 are turned on and switches Q4-Q7 are turned off, so that the resonant capacitors C1-C2 are connected in series with each other and then connected in series with the inductor L between the first voltage V1 and the second voltage V2, forming a first current path for charging. In the second program, according to the second operation signal GB, switches Q4-Q7 are turned on and switches Q1-Q3 are turned off, so that the resonant capacitors C1-C2 are connected in parallel with each other and then connected in series with the inductor L between the second voltage V2 and the ground potential, forming multiple second current paths for discharging. It should be noted that the first program and the second program are repeatedly alternated at different time periods, rather than simultaneously, to convert the first voltage V1 to the second voltage V2 or the second voltage V2 to the first voltage V1. In this embodiment, the DC bias voltage of each resonant capacitor C1 to C2 is the second voltage V2. Therefore, the resonant capacitors C1 to C2 in this embodiment need to withstand a lower rated voltage, so smaller capacitors can be used.

[0197] The control circuit 1901 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0198] In one embodiment, the voltage conversion ratio of the first voltage V1 to the second voltage V2 of the switching capacitor voltage conversion circuit 190 can be 3:1 or 2:1.

[0199] Figure 27 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 27 As shown, the switching capacitor voltage conversion circuit 200 of the present invention includes a resonant capacitor C3, non-resonant capacitors C1 to C2, switches Q1 to Q8, and an inductor L.

[0200] Switches Q1-Q8 can switch the electrical connection relationship between the corresponding resonant capacitor C3, non-resonant capacitors C1-C2, and inductor L according to the corresponding operation signals. In the first program, according to the first operation signal GA, switches Q1, Q3, Q5, and Q7 are turned on, while switches Q2, Q4, Q6, and Q8 are turned off. This causes the non-resonant capacitors C1 and C3 to be connected in series with the inductor L between the first voltage V1 and the second voltage V2. One end of the non-resonant capacitor C2 is coupled between the non-resonant capacitor C1 and the resonant capacitor C3, while the other end is coupled to ground, forming a first current path for the charging program. In the second program, according to the second operation signal GB, switches Q2, Q4, Q6, and Q8 are turned on, while switches Q1, Q3, Q5, and Q7 are turned off. This causes the resonant capacitor C3 to be connected in series with the inductor L between the second voltage V2 and the ground, forming a second current path for the discharging program. It should be noted that the first procedure and the second procedure described above are repeated and interleaved at different time periods, rather than being performed simultaneously, in order to convert the first voltage V1 into the second voltage V2 or the second voltage V2 into the first voltage V1.

[0201] The control circuit 2001 in this embodiment can be adopted. Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. For example... Figure 27 As shown, when the control circuit 2001 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program and / or the second program, and when multiple switches (e.g., switches Q1 to Q8) are not turned on, one end of the corresponding inductor L is connected to the body diode (e.g., in at least one switch Q8 and Q7) via an internal diode (body diode). Figure 27 (As shown by the dashed line) and is switched to a DC potential, so that the inductor current ILo flowing toward the second voltage V2 is a linear ramp current, in order to adjust the preset ratio.

[0202] Figure 28 This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to yet another embodiment of the present invention. Figure 28 As shown, the switching capacitor voltage conversion circuit 210 of the present invention includes a resonant capacitor C3, non-resonant capacitors C1 to C2, switches Q1 to Q6, and an inductor L.

[0203] Switches Q1-Q6 can switch the electrical connection relationship between the corresponding resonant capacitor C3, non-resonant capacitors C1-C2, and inductor L according to the corresponding operation signals. In the first program, according to the first operation signal GA, switches Q1, Q3, and Q5 are turned on, while switches Q2, Q4, and Q6 are turned off. This causes the non-resonant capacitor C2 and the resonant capacitor C3 to be connected in parallel and then connected in series with the non-resonant capacitor C1 and inductor L between the first voltage V1 and the second voltage V2, forming a first current path for charging. In the second program, according to the second operation signal GB, switches Q2, Q4, and Q6 are turned on, while switches Q1, Q3, and Q5 are turned off. This causes the resonant capacitor C3 and the inductor L to be connected in series between the second voltage V2 and the ground potential, forming a second current path for discharging. It should be noted that the first program and the second program are repeatedly alternated at different time periods, rather than simultaneously, to convert the first voltage V1 to the second voltage V2 or the second voltage V2 to the first voltage V1.

[0204] The control circuit 2101 in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. For example... Figure 28 As shown, when the control circuit 2101 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program and / or the second program, and when multiple switches (e.g., switches Q1 to Q6) are not turned on, one end of the corresponding inductor L is connected to the body diode (e.g., in at least one switch Q5 and Q6) via an internal diode (body diode). Figure 28 (As shown by the dashed line) and is switched to a DC potential, so that the inductor current ILo flowing toward the second voltage V2 is a linear ramp current, in order to adjust the preset ratio.

[0205] Figure 29 This is a circuit diagram showing a switching capacitor voltage conversion circuit according to another embodiment of the present invention. Figure 29 As shown, the switching capacitor voltage conversion circuit 220 of the present invention includes a resonant capacitor C3, non-resonant capacitors C1 to C2, switches Q1 to Q8, and an inductor L.

[0206] Switches Q1-Q8 can switch the electrical connection relationship between the corresponding resonant capacitor C3, non-resonant capacitors C1-C2, and inductor L according to the corresponding operation signals. In the first program, according to the first operation signal GA, switches Q1, Q2, Q5, and Q6 are turned on, while switches Q3, Q4, Q7, and Q8 are turned off. This causes the non-resonant capacitor C1, the resonant capacitor C3, and the inductor L to be connected in series between the first voltage V1 and the second voltage V2. One end of the non-resonant capacitor C2 is coupled between the non-resonant capacitor C1 and the resonant capacitor C3, while the other end of the non-resonant capacitor C2 is coupled to ground potential, forming a first current path for the charging program. In the second program, according to the second operation signal GB, switches Q3, Q4, Q7, and Q8 are turned on, while switches Q1, Q2, Q5, and Q6 are turned off. This causes the resonant capacitor C3 and the inductor L to be connected in series between the second voltage V2 and the ground potential, forming a second current path for the discharging program. It should be noted that the first procedure and the second procedure described above are repeated and interleaved at different time periods, rather than being performed simultaneously, in order to convert the first voltage V1 into the second voltage V2 or the second voltage V2 into the first voltage V1.

[0207] The control circuit 2201 in this embodiment can be adopted Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. The way inductor current freewheels is similar to... Figure 2C Please refer to the information about Figure 2C A detailed description.

[0208] Figure 30 This is a circuit diagram illustrating a switching capacitor voltage conversion circuit according to yet another embodiment of the present invention. Figure 30 As shown, the switching capacitor voltage conversion circuit 230 of the present invention includes resonant capacitors C1 to C3, switches Q1 to Q10, and inductor L.

[0209] Switches Q1-Q10 can switch the electrical connection between the corresponding resonant capacitors C1-C3 and the inductor L according to the corresponding operation signals. In the first program, according to the first operation signal GA, switches Q1, Q3, Q5, Q8, and Q9 are turned on, while switches Q2, Q4, Q6, Q7, and Q10 are turned off. This causes the resonant capacitors C1 and C3 to be connected in series with the inductor L between the first voltage V1 and the second voltage V2. One end of the resonant capacitor C2 is coupled between the resonant capacitors C1 and C3, while the other end of the resonant capacitor C2 is coupled to ground potential, thus forming a first current path for charging. In the second procedure, according to the second operation signal GB, switches Q2, Q4, Q6, Q7, and Q10 are turned on, while switches Q1, Q3, Q5, Q8, and Q9 are turned off. This causes resonant capacitors C1 and C2 to be connected in series, then in parallel with resonant capacitor C3, and finally in series with inductor L between the second voltage V2 and ground potential, forming a second current path for the discharge procedure. It should be noted that the first and second procedures described above are repeated and interleaved at different time intervals, rather than simultaneously, to convert the first voltage V1 to the second voltage V2 or vice versa.

[0210] The control circuit 2301 in this embodiment can be adopted as follows: Figure 2A and Figure 2B The control circuit architecture should be implemented accordingly. Please refer to the relevant documentation. Figure 2A and Figure 2B A detailed description. For example... Figure 30 As shown, when the control circuit 2301 reduces the duty cycle of the first operation signal GA and / or the second operation signal GB according to a preset ratio, in the first program and / or the second program, and when multiple switches (e.g., switches Q1 to Q10) are not turned on, one end of the corresponding inductor L is connected to the body diode (e.g., in at least one switch (e.g., switches Q10 and Q9)) via an internal diode (body diode). Figure 30 (As shown by the dashed line) and is switched to a DC potential, so that the inductor current ILo flowing toward the second voltage V2 is a linear ramp current, in order to adjust the preset ratio.

[0211] As described above, the present invention provides a switching capacitor voltage conversion circuit, which can improve power conversion efficiency, reduce switching losses, reduce voltage stress on switches and inductors, reduce inductor size, and make the output voltage adjustable by adjusting the duty cycle and / or operating frequency and allowing the inductor current to freewheel.

[0212] The present invention has been described above with reference to preferred embodiments. However, the above description is only intended to facilitate understanding of the invention by those skilled in the art and is not intended to limit the broadest scope of the invention. The described embodiments are not limited to individual application and can also be used in combination. For example, two or more embodiments can be used in combination, and some components of one embodiment can be used to replace corresponding components in another embodiment. Furthermore, within the same spirit of the invention, those skilled in the art can conceive of various equivalent changes and combinations. For example, the phrase "processing or calculating based on a signal or generating an output result" in the present invention is not limited to the signal itself, but also includes, when necessary, performing voltage-to-current conversion, current-to-voltage conversion, and / or proportional conversion on the signal, and then processing or calculating based on the converted signal to generate an output result. Therefore, within the same spirit of the invention, those skilled in the art can conceive of various equivalent changes and combinations, and there are many combinations, which will not be listed here. Therefore, the scope of the present invention should cover the above and all other equivalent changes.

Claims

1. A switched-capacitor voltage conversion circuit for converting a first voltage to a second voltage or converting the second voltage to the first voltage, the switched-capacitor voltage conversion circuit comprising: a switched-capacitor converter coupled between the first voltage and the second voltage; and a control circuit for generating a control signal to control the switched-capacitor converter to convert the first voltage to the second voltage or convert the second voltage to the first voltage; wherein the switched-capacitor converter comprises: at least one resonant capacitor; a plurality of switches coupled with the at least one resonant capacitor; and at least one inductor; wherein the control circuit is configured to generate the control signal, the control signal comprising a first operation signal and a second operation signal, wherein the first operation signal is configured to operate a plurality of first switches of the plurality of switches, and the second operation signal is configured to operate a plurality of second switches of the plurality of switches; wherein in a first procedure, the plurality of first switches are controlled to switch by the first operation signal to cause the at least one resonant capacitor and a corresponding inductor to be connected in series between the first voltage and the second voltage to form a first current path and operate in resonance; wherein in at least one second procedure, the plurality of second switches are controlled to switch by the second operation signal to cause the at least one resonant capacitor and a corresponding inductor to be connected in series between the second voltage and a DC potential to form or alternately form a plurality of second current paths and operate in resonance; wherein the plurality of first switches are turned on during a first time period and the plurality of second switches are turned on during a second time period, the first time period and the second time period being non-overlapping with each other, such that the first procedure and the at least one second procedure are non-overlapping with each other; wherein the control circuit is configured to adjust an operation frequency and / or a duty cycle of the first operation signal and / or the second operation signal according to a preset ratio to adjust a ratio between the first voltage and the second voltage to the preset ratio; wherein the first procedure and the at least one second procedure are repeatedly interleaved with each other to convert the first voltage to the second voltage or convert the second voltage to the first voltage; wherein when the control circuit adjusts the duty cycle of the first operation signal and / or the second operation signal according to the preset ratio in the first procedure and / or the second procedure, and the plurality of first switches and / or the plurality of second switches are turned on, an inductor current flowing towards the second voltage is in a first state, wherein the first state is that the inductor current flowing towards the second voltage is a resonant current, when the control circuit adjusts the duty cycle of the first operation signal and / or the second operation signal according to the preset ratio in the first procedure and / or the second procedure, the inductor current flowing through the corresponding inductor is freewheeled through a freewheeling path, thereby causing the inductor current flowing towards the second voltage to be in a second state, such that the corresponding inductor performs inductive power conversion switching between the first state and the second state. the second state is that the inductor current flowing towards the second voltage is a non-resonant current.

2. The switched-capacitor voltage conversion circuit of claim 1, wherein, the second state is that the inductor current stops flowing towards the second voltage, or the inductor current flowing towards the second voltage is a linear ramp current.

3. The switched-capacitor voltage conversion circuit of claim 2, wherein, ​ 4. The switched-capacitor voltage conversion circuit of claim 3, wherein, When the first switches and the second switches are all non-conductive in the first procedure and / or the second procedure, the inductor current in the second state flows through the current freewheeling path including the internal diode of the corresponding switch.

5. The switched-capacitor voltage conversion circuit of claim 4, wherein, When the control circuit adjusts the duty cycle of the first operation signal and / or the second operation signal according to the preset ratio, in the first procedure and / or the second procedure, and the first switches and the second switches are all non-conductive, one end of the corresponding inductor is conducted to the DC potential through the internal diode of at least one of the switches, so that the inductor current flowing towards the second voltage is the linear ramp current, to adjust the preset ratio.

6. The switched-capacitor voltage conversion circuit of claim 4, wherein, When the control circuit adjusts the duty cycle of the first operation signal and / or the second operation signal according to the preset ratio, in the first procedure and / or the second procedure, and the first switches and the second switches are all non-conductive, the inductor current flowing through the corresponding inductor is conducted through the internal diode of at least one of the switches, and the current freewheels through a closed loop formed by a resonance tank and the internal diode of at least one of the switches, thereby making the second state that the inductor current stops flowing towards the second voltage, wherein the at least one resonance capacitor and the at least one inductor form the resonance tank.

7. The switched-capacitor voltage conversion circuit of claim 1, wherein, In the first procedure and / or the second procedure, after the inductor current flowing through the corresponding inductor decreases to 0, the switches remain non-conductive for a zero-current period.

8. The switched-capacitor voltage conversion circuit of claim 2, wherein, A non-resonant capacitor is further included and coupled with the resonance capacitor, wherein the voltage across the non-resonant capacitor is maintained at a fixed DC voltage in the first procedure and the second procedure.

9. The switched-capacitor voltage conversion circuit of claim 2, wherein, The first voltage is twice the second voltage, and the first operation signal and the second operation signal have respective corresponding operation frequencies.

10. The switched-capacitor voltage conversion circuit of claim 9, wherein, The duty cycles of the first operation signal and the second operation signal are both 50%.

11. The switched-capacitor voltage conversion circuit of claim 2, wherein, The preset ratio is the ratio of the first voltage to the second voltage, and the operation frequency of the first operation signal and / or the second operation signal is positively correlated with the preset ratio.

12. The switched-capacitor voltage conversion circuit of claim 2, wherein, The operation frequency of the first operation signal is higher than the resonance frequency of the at least one resonance capacitor and the corresponding inductor in the first procedure, and the operation frequency of the second operation signal is higher than the resonance frequency of the at least one resonance capacitor and the corresponding inductor in the second procedure.

13. The switched-capacitor voltage conversion circuit of claim 2, wherein, The preset ratio is a positive integer not less than 2.

14. The switched-capacitor voltage conversion circuit of claim 2, wherein, The switching capacitor converter includes a distributed switching capacitor converter, a series-parallel switching capacitor converter, a Dickson switching capacitor converter, a ladder switching capacitor converter, a voltage doubler switching capacitor converter, a Fibonacci switching capacitor converter, a pipeline switching capacitor converter, or a switched cavity converter.

15. The switched-capacitor voltage conversion circuit of claim 14, wherein, The series-parallel switching capacitor converter includes a one-half series-parallel switching capacitor converter, a one-third series-parallel switching capacitor converter, or a one-fourth series-parallel switching capacitor converter.

16. The switched-capacitor voltage conversion circuit of claim 2, wherein, The DC potential is a ground potential.

17. The switched-capacitor voltage conversion circuit of claim 2, wherein, The control circuit includes: a current sensing circuit for sensing the current flowing through the at least one inductor to generate at least one current sensing signal; and A control signal generating circuit coupled to the current sensing circuit for generating the control signal according to the current sensing signal and the preset ratio.

18. A switched-capacitor voltage conversion method for converting a first voltage to a second voltage or converting the second voltage to the first voltage, the switched-capacitor voltage conversion method comprising: operating a plurality of first switches with a first operation signal; operating a plurality of second switches with a second operation signal; in a first procedure, controlling switching of the plurality of first switches by the first operation signal to cause at least one resonant capacitor and a corresponding inductor to be connected in series between the first voltage and the second voltage to form a first current path and operate in resonance; in at least one second procedure, controlling switching of the plurality of second switches by the second operation signal to cause the at least one resonant capacitor and the corresponding inductor to be connected in series between the second voltage and a DC potential to form or alternately form a plurality of second current paths and operate in resonance; and adjusting an operating frequency and / or a duty cycle of the first operation signal and / or the second operation signal according to a preset ratio to adjust a ratio between the first voltage and the second voltage to the preset ratio; wherein the on duration of the plurality of first switches and the on duration of the plurality of second switches do not overlap with each other to cause the first procedure and the second procedure to not overlap with each other; wherein the first procedure and the at least one second procedure are repeatedly interleaved with each other to convert the first voltage to the second voltage or convert the second voltage to the first voltage; wherein when the duty cycle of the first operation signal and / or the second operation signal is adjusted according to the preset ratio to be reduced in the first procedure and / or the second procedure, and the plurality of first switches and / or the plurality of second switches are on, an inductor current flowing towards the second voltage is in a first state, wherein the first state is that the inductor current flowing towards the second voltage is a resonant current, when the duty cycle of the first operation signal and / or the second operation signal is adjusted according to the preset ratio to be reduced, the inductor current flowing through the corresponding inductor is commutated through a current commutation path, thereby causing the inductor current flowing towards the second voltage to be in a second state, such that the corresponding inductor performs inductive power conversion switching between the first state and the second state.

19. The switched-capacitor voltage conversion method of claim 18, wherein, the second state is that the inductor current flowing towards the second voltage is a non-resonant current.

20. The switched-capacitor voltage conversion method of claim 19, wherein, the second state is that the inductor current stops flowing towards the second voltage, or the inductor current flowing towards the second voltage is a linear ramp current.

21. The switched-capacitor voltage conversion method of claim 20, wherein, in the first procedure and / or the second procedure, when the plurality of first switches and the plurality of second switches are not on, the inductor current is in the second state, and the current commutation path through which the inductor current flows includes a body diode in the corresponding switch.

22. The switched-capacitor voltage conversion method of claim 21, wherein, When the duty cycle of the first operation signal and / or the second operation signal is adjusted according to the preset ratio, in the first procedure and / or the second procedure, and the plurality of first switches and the plurality of second switches are not turned on, one end of the corresponding inductor is turned on to the DC potential via the internal diode in the at least one switch in the plurality of first switches and the plurality of second switches, so that the inductor current flowing towards the second voltage is the linear ramp current, to adjust the preset ratio.

23. The switched-capacitor voltage conversion method of claim 21, wherein, When the duty cycle of the first operation signal and / or the second operation signal is adjusted according to the preset ratio, in the first procedure and / or the second procedure, and the plurality of first switches and the plurality of second switches are not turned on, the inductor current flowing through the corresponding inductor is turned on via the internal diode in the at least one switch in the plurality of first switches and the plurality of second switches, and continues to flow through a closed loop formed by a resonance tank and the internal diode in the at least one switch, thereby making the second state the inductor current stops flowing towards the second voltage, wherein the at least one resonance capacitor and the corresponding inductor form the resonance tank.

24. The switched-capacitor voltage conversion method of claim 18, wherein, In the first procedure and / or the second procedure, after the inductor current flowing through the corresponding inductor decreases to 0, the plurality of first switches and the plurality of second switches remain not turned on for a zero current period.

25. The switched-capacitor voltage conversion method of claim 19, wherein, Also comprising providing a non-resonant capacitor coupled with the resonance capacitor, wherein the cross voltage of the non-resonant capacitor is maintained at a fixed DC voltage in the first procedure and the second procedure.

26. The switched-capacitor voltage conversion method of claim 19, wherein, The first voltage is twice the second voltage, and the first operation signal and the second operation signal have their respective corresponding operation frequencies.

27. The switched-capacitor voltage conversion method of claim 26, wherein, The duty cycles of the first operation signal and the second operation signal are both 50%.

28. The switched-capacitor voltage conversion method of claim 19, wherein, The preset ratio is the ratio of the first voltage to the second voltage, and the operation frequency of the first operation signal and / or the second operation signal is positively correlated with the preset ratio.

29. The switched-capacitor voltage conversion method of claim 19, wherein, The operation frequency of the first operation signal is higher than the resonance frequency of the at least one resonance capacitor and the corresponding inductor in the first procedure, and the operation frequency of the second operation signal is higher than the resonance frequency of the at least one resonance capacitor and the corresponding inductor in the second procedure.

30. The switched-capacitor voltage conversion method of claim 19, wherein, The preset ratio is a positive integer not less than 2.

31. The switched-capacitor voltage conversion method of claim 19, wherein, Also comprising providing a switching capacitor converter, the switching capacitor converter providing the plurality of first switches, the plurality of second switches, the at least one resonance capacitor, and the inductor, wherein the switching capacitor converter includes a distributed switching capacitor converter, a series-parallel switching capacitor converter, a Dickson switching capacitor converter, a ladder switching capacitor converter, a voltage doubler switching capacitor converter, a Fibonacci switching capacitor converter, a pipeline switching capacitor converter, or a switched cavity converter.

32. The switched-capacitor voltage conversion method of claim 31, wherein, The series-parallel switching capacitor converter includes a one-half series-parallel switching capacitor converter, a one-third series-parallel switching capacitor converter, or a one-fourth series-parallel switching capacitor converter.

33. The switched-capacitor voltage conversion method of claim 19, wherein, The DC potential is a ground potential.

34. The switched-capacitor voltage conversion method of claim 19, wherein, Also comprising: sensing the current flowing through the at least one inductor to generate at least one current sensing signal; and The first operation signal and / or the second operation signal are generated according to the current sensing signal and the preset ratio.

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