Inverter power control method and system

Abstract

The application discloses an inverter power control method and system, and relates to the technical field of grid-connected inverter control. The application aims at the problems of low active power control bandwidth and slow power response speed of a voltage control type grid-connected inverter under a weak power grid, especially an extremely weak power grid, and provides an inverter power control method. The method improves the active power control bandwidth through differential feedforward control of a given power instruction, and does not affect the system stability. Meanwhile, the method detects the response time through a timing injection power step disturbance, and adjusts the feedforward coefficient in real time according to the response time, so as to achieve the goal of adapting to the impedance change of the power grid.

Description

TECHNICAL FIELD

[0001] The present application relates to the technical field of grid-connected inverter control, and particularly relates to an inverter power control method and system. BACKGROUND

[0002] As a key interface of new energy grid-connected, the control mode of grid-connected inverter is a key factor affecting the stable and efficient operation of new energy grid-connected power generation system. With the continuous improvement of new energy penetration, the resonance instability problem of traditional current-controlled inverters under weak grids is increasingly prominent. Voltage-controlled inverters have strong stability under weak grids and extremely weak grids, and have attracted more and more attention in recent years. However, the active power control bandwidth of voltage-controlled inverters under weak grids, especially extremely weak grids, is low, the power response speed is slow, and it is difficult to realize the high-efficiency MPPT function. At present, there are many academic papers on the problem of low active power control bandwidth of voltage-controlled inverters, for example:

[0003] 1) The paper titled "Adjusting Synchronverter Dynamic Response Speed via Damping Correction Loop" (S. Dong and Y. C. Chen, IEEE Transactions on Energy Conversion, vol. 32, no. 2, pp. 608-619, June 2017) proposes to adjust the dynamic response speed by adding a damping correction control, but this scheme introduces a differential action in the power feedback channel, which may amplify noise and even lead to instability.

[0004] 2) The paper titled "Virtual Inertia Control Strategy of Virtual Synchronous Generator Based on Differential Compensation Link" (Xu Haizhen, Zhang Xing, Liu Fang, Shi Rongliang, Hu Chao, Ni Hua. Power System Automation, 2017, 41(03): 96-102) proposes a VSG control strategy based on differential compensation link virtual inertia, which adds a differential compensation link in the forward channel to improve the power dynamic response speed. However, this scheme will affect the stability of the system due to the introduction of differential compensation.

[0005] 3) The paper titled "Rapid Power Control and MPPT Method of Voltage Controlled Grid-connected Inverters In Very Weak Grids" (Z. Guo et al. 2021 IEEE 16th Conference on Industrial Electronics and Applications (ICIEA), 2021, pp. 1557-1563) proposes a rapid active power control method for voltage-controlled grid-connected inverters based on outer loop modification and power command pre-filtering. However, this method is complex to design and cannot adapt to changes in grid impedance.

[0006] In summary, the existing technology has the following shortcomings:

[0007] 1. The existing literature proposes methods to improve the dynamic response speed of power, which ignores the impact on stability. Improving the power response speed may cause system instability.

[0008] 2. The existing literature proposes methods to improve the dynamic response speed of power, which do not take into account the changes in grid impedance. In actual systems, grid impedance often fluctuates significantly. In this case, a well-designed control strategy or control parameters may no longer be applicable. SUMMARY

[0009] To overcome the limitations of the above solutions, the present application proposes an inverter power control method and system. The control method improves the dynamic response speed of active power by feeding forward control of the differential of the given power command, without affecting system stability. By injecting power step disturbances at regular intervals, the response time is detected, and the feedforward coefficient is adjusted in real time to adapt to changes in grid impedance.

[0010] The purpose of the present application is achieved as follows. The present application provides an inverter power control method, comprising the following steps:

[0011] Step 1, set the given active power command signal P set , the given reactive power command signal Q set , inject a step disturbance signal ΔP set into the set given active power command signal P ref at the same time interval, to obtain the active input power command signal P ref and the reactive input power command signal Q ref ;

[0012] Step 2, sample the output grid-connected three-phase current iga , i gb , i gc and the common coupling point three-phase voltage u pcca , u pccb , u pccc , the output grid-connected current αβ-axis component i gα , i gβ and the common coupling point voltage αβ-axis component u pccα , u pccβ ; and the output grid-connected current dq-axis component i gd , i gq and the common coupling point voltage dq-axis component u pccd , u pccq ;

[0013] Step 3, the active power signal gα , i gβ and the common coupling point voltage αβ-axis component u pccα , u pccβ is calculated by the grid-connected current αβ-axis component i and the reactive power signal , and the active grid-connected power P e and the reactive grid-connected power Q e are obtained by a low-pass filter;

[0014] Step 4, when the absolute value of the difference between the active grid-connected power P e and the active input power instruction signal P ref is less than or equal to a set multiple of the step disturbance signal ΔP ref , the count value T is recorded and the counting is ended;

[0015] Step 5, the given power instruction feedforward coefficient K f is obtained by modifying the count value T;

[0016] Step 6, the frequency signal ω and the d-axis voltage instruction signal u dref are obtained by the feedforward coefficient K f , the reactive input power instruction signal Q ref and the power fast control equation;

[0017] Step 7, the angle signal θ is obtained by the frequency signal ω and integral control;

[0018] Step 8, the current instruction signal dq-axis component i pccq is obtained by the given q-axis voltage instruction signal u qref , the common coupling point voltage dq-axis component u pccd , u pccq and the voltage closed-loop control equation.dref , i qref ;

[0019] Step 9, get the inverter control signal dq-axis component u dref , i qref , output grid-connected current dq-axis component i gd , i gq and current closed-loop control equation d , u q ;

[0020] Step 10, get the inverter control signal u d , u q under three-phase static coordinate system through the transformation equation from two-phase rotating coordinate system to three-phase static coordinate system a , u b , u c .

[0021] Preferably, the calculation formula of the active input power command signal P ref and the reactive input power command signal Q ref in step 1 is respectively:

[0022] P ref = P set + ΔP ref

[0023] Q ref = Q set .

[0024] Preferably, the calculation formula of the active power signal and the reactive power signal in step 3 is respectively:

[0025]

[0026]

[0027] Preferably, in step 4: the setting multiple of ΔP ref is 0.1.

[0028] Preferably, the solving process of the given power command feedforward coefficient K f in step 5 is:

[0029] First, set the step disturbance signal ΔP ref to zero after counting is completed, and then set the given power command feedforward coefficient K f according to the following:

[0030]

[0031] In the formula, N is a given correction coefficient.

[0032] Preferably, the expression for the power fast control equation in step 6 is:

[0033]

[0034]

[0035] In the formula, ω n V is the system's rated angular frequency. nAmp T is the rated line voltage amplitude. droop Let be the time constant of the given power feedforward low-pass filter, s be the Laplace operator, m be the active droop coefficient, and n be the reactive droop coefficient.

[0036] Preferably, the expression for the angle signal θ in step 7 is:

[0037]

[0038] In the formula, s is the Laplace operator.

[0039] Preferably, the expression for the voltage closed-loop control equation in step 8 is:

[0040] i dref =(K vp +K vi / s)(u dref -u pccd )

[0041] i qref =(K vp +K vi / s)(u qref -u pccq )

[0042] In the formula, K vp K is the proportional coefficient of the voltage closed-loop control PI regulator. vi is the integral coefficient of the voltage closed-loop control PI regulator, and s is the Laplace operator.

[0043] Preferably, the expression for the current closed-loop control equation in step 9 is:

[0044] u d =(K ip +K ii / s)(i dref -i gd )

[0045] u q =(K ip +K ii / s)(i qref-i gq )

[0046] In the formula, K ip K is the proportional coefficient of the PI regulator in the current closed-loop control. ii is the integral coefficient of the current closed-loop control PI regulator, and s is the Laplace operator.

[0047] Preferably, the expression for the inverter control signal in step 10 is:

[0048]

[0049] The present invention also provides an inverter power control system, comprising:

[0050] A three-phase full-bridge inverter circuit is connected in series with the DC power supply U. dc and filter inductor L f Between, the filter capacitor C f Connected in parallel to the filter inductor L f Equivalent inductance L of grid connection g Between, the grid-connected equivalent inductance L g Connect to three-phase power grid E g The main circuit topology of the grid-connected inverter; used to provide the active power command signal P. set Inject a step disturbance signal ΔP ref Disturbance module; used for sampling the output grid-connected three-phase current i ga i gb i gc and the three-phase voltage u at the common coupling point pcca u pccb u pccc The sampling output module is used to obtain the αβ axis component I of the output grid-connected current. gα i gβ and the common coupling point voltage αβ axis component u pccα u pccβ The coordinate system transformation module is used to obtain the dq-axis components of the output grid-connected current. gd i gq and the dq-axis component of the voltage at the common coupling point u pccd u pccq The coordinate system transformation module is used to calculate the active power signal. and reactive power signal The calculation module is used to obtain the active power P connected to the grid. e Reactive power connected to the grid Q e The low-pass filter module is used to record the active power P connected to the grid. e With active input power command signal P ref The absolute value of the difference is less than or equal to a set multiple of the step disturbance signal ΔP. refa count module for counting the number of times the power reference value T is greater than the power value P f a correction module for obtaining a frequency signal ω and a d-axis voltage reference signal u dref a calculation module for obtaining an angle signal θ by integrating the frequency signal ω qref a voltage reference signal input module, and a current reference signal dq component i dref , i qref a calculation module for obtaining inverter control signals dq component u d , u q a calculation module for obtaining u d , u q inverter control signals u a , u b , u c a coordinate system transformation module; and a microprocessor and a memory, each of the modules, microprocessor being programmed or configured to perform the steps of the inverter power control method of any one of claims 1-10.

[0051] The present application also provides a computer readable storage medium having stored therein a computer program that is programmed or configured to perform the inverter power control method of any one of claims 1-10.

[0052] Compared with the prior art, the present application has the following advantages:

[0053] 1. The present application significantly improves the active power control bandwidth, and improves the power dynamic response speed without affecting the system stability.

[0054] 2. The present application can adapt to the change of grid impedance, and real-time detect the power response time by injecting power step disturbance at regular intervals, and adaptively adjust the control parameters. BRIEF DESCRIPTION OF DRAWINGS

[0055] Figure 1 is a flow chart of the control method of the present application.

[0056] Figure 2 is a grid-connected inverter main circuit topology in the simulation of the present application.

[0057] Figure 3 is the power given and response waveform without adding the control scheme of the present application when the grid impedance is 15mH.

[0058] Figure 4Power reference and response waveforms with the control scheme of the present application for grid impedance 15mH.

[0059] Figure 5 Power reference and response waveforms without the control scheme of the present application for grid impedance 4mH.

[0060] Figure 6 Power reference and response waveforms with the control scheme of the present application for grid impedance 4mH. DETAILED DESCRIPTION

[0061] The technical solutions of the present application are further described below in combination with the drawings.

[0062] Figure 1 Flow chart of the control method of the present application. As can be seen from the chart, the present application provides an inverter power control method, comprising the following steps:

[0063] Step 1, setting given active power command signal P set , given reactive power command signal Q set , injecting a step disturbance signal ΔP set into the given active power command signal P ref every 5s, obtaining active input power command signal P ref and reactive input power command signal Q ref .

[0064] In the present embodiment, the calculation formulae of the active input power command signal P ref and the reactive input power command signal Q ref are respectively:

[0065] P ref = P set + ΔP ref

[0066] Q ref = Q set .

[0067] In the present embodiment, ΔP ref = 3%P N , P N is rated power, and P N = 20000W.

[0068] Step 2, sampling output grid-connected current i ga , i gb , i gc and common coupling point voltage u pcca , u pccb , u pcccThen, the output grid-connected current αβ-axis component i gα , i gβ and the point of common coupling voltage αβ-axis component u pccα , u pccβ are obtained through Clarke transformation from three-phase static coordinate system to two-phase static coordinate system.

[0069] Step 3, the output grid-connected current i ga , i gb , i gc and the point of common coupling voltage u pcca , u pccb , u pccc are obtained through Park transformation from three-phase static coordinate system to two-phase rotating coordinate system. gd , i gq and the point of common coupling voltage dq-axis component u pccd , u pccq .

[0070] Step 4, the active power signal and the reactive power signal are calculated and the active grid-connected power P e and the reactive grid-connected power Q e are obtained through low-pass filter.

[0071] In this embodiment, the calculation formulae of the active power signal and the reactive power signal are respectively:

[0072]

[0073]

[0074] Step 5, a counter is set, and the counting is ended when the absolute value of the difference between the active grid-connected power P e and the active input power instruction signal P ref is less than or equal to 0.1ΔP ref , and the counting value T is recorded.

[0075] Step 6, the given power instruction feedforward coefficient K f is obtained through coefficient correction of the counting value T.

[0076] In this embodiment, the solving process of the given power instruction feedforward coefficient K f is as follows:

[0077] Firstly, the step disturbance signal ΔP ref is set to zero after the counting is completed, and then the given power instruction feedforward coefficient K f is set according to the following formula:

[0078]

[0079] In the formula, N is a given correction coefficient. In this embodiment, N = 300.

[0080] Step 7: Obtain the frequency signal ω and the d-axis voltage command signal u through the power fast control equation. dref .

[0081] In this embodiment, the expression for the fast power control equation is:

[0082]

[0083]

[0084] In the formula, ω n V is the system's rated angular frequency. nAmp T is the rated line voltage amplitude. droop Let be the time constant of the given power feedforward low-pass filter, s be the Laplace operator, m be the active droop coefficient, and n be the reactive droop coefficient.

[0085] In this embodiment, ω n =100π, T droop =0.05s, m=0.0001413, n=0.0010885.

[0086] Step 8: Obtain the angle signal θ through integral control.

[0087] In this embodiment, the expression for the angle signal θ is:

[0088]

[0089] Step 9, give the q-axis voltage command signal u qref The current command signal dq-axis component i is obtained through the voltage closed-loop control equation. dref i qref .

[0090] In this embodiment, the expression for the voltage closed-loop control equation is:

[0091] i dref =(K vp +K vi / s)(u dref -u pccd )

[0092] i qref =(K vp +K vi / s)(uqref -u pccq )

[0093] wherein K vp is the proportional coefficient of the voltage closed-loop control PI regulator, K vi is the integral coefficient of the voltage closed-loop control PI regulator.

[0094] In this embodiment, K vp = 0.05, K vi = 120, and u qref = 0.

[0095] Step 10, obtaining the inverter control signal dq-axis component u d , u q by the current closed-loop control equation.

[0096] In this embodiment, the expression of the current closed-loop control equation is:

[0097] u d = (K ip + K ii / s)(i dref - i gd )

[0098] u q = (K ip + K ii / s)(i qref - i gq )

[0099] wherein K ip is the proportional coefficient of the current closed-loop control PI regulator, K ii is the integral coefficient of the current closed-loop control PI regulator.

[0100] In this embodiment, K ip = 4, K ii = 10.

[0101] Step 11, obtaining the inverter control signals u a , u b , u c in the three-phase static coordinate system by the transformation equation from the two-phase rotating coordinate system to the three-phase static coordinate system.

[0102] In this embodiment, the inverse Park transformation equation is:

[0103]

[0104] The inverter control signals u a , u b , u cThe switch signal of the inverter power device is generated through SVPWM modulation, and the opening and closing of the three-phase full-bridge inverter power device are controlled through the drive protection circuit.

[0105] The application further provides an inverter power control system, comprising:

[0106] The three-phase full-bridge inverter circuit is connected in series between the DC side power supply U dc and the filter inductance L f The filter capacitance C f is connected in parallel between the filter inductance L f and the grid equivalent inductance L g The grid equivalent inductance L g is connected to the three-phase power grid E g to form a grid-connected inverter main circuit topology; a given active power command signal P set is injected into a first-order step disturbance signal ΔP ref The disturbance module is used for sampling the output grid-connected three-phase current I ga , i gb , i gc and the sampling output module of the three-phase voltage u pcca , u pccb , u pccc at the point of common coupling; the coordinate system transformation module is used to obtain the output grid-connected current αβ-axis component i gα , i gβ and the αβ-axis component u pccα , u pccβ of the voltage at the point of common coupling; the coordinate system transformation module is used to obtain the output grid-connected current dq-axis component i gd , i gq and the dq-axis component u pccd , u pccq of the voltage at the point of common coupling; the calculation module is used to calculate the active power signal and the reactive power signal ; the low-pass filter module is used to obtain the active grid-connected power P e and the reactive grid-connected power Q e ; the counting module is used to record the absolute value of the difference between the active grid-connected power P e and the active input power command signal P ref is less than or equal to the set multiple of the step disturbance signal ΔP ref ; the correction module is used to obtain the given power command feedforward coefficient K f after the coefficient correction of the counting value T dref ; the calculation module is used to obtain the frequency signal ω and the d-axis voltage command signal u dref through the power fast control equation; the calculation module is used to obtain the angle signal θ through the frequency signal ω and integral control; the calculation module is used to obtain the q-axis voltage command signal u qrefThe voltage command signal input module; and the current command signal dq-axis component i obtained through the voltage closed-loop control equation. dref i qref The calculation module is used to obtain the dq-axis component u of the inverter control signal through the current closed-loop control equation. d u q The calculation module; used to convert u d u q The inverter control signal u is obtained through coordinate system transformation. a u b u c The coordinate system transformation module; and a microprocessor and a memory, each of the modules and the microprocessor being programmed or configured to perform the steps of the inverter power control method according to any one of claims 1 to 10.

[0107] The present invention also provides a computer-readable storage medium storing a computer program programmed or configured to perform the inverter power control method according to any one of claims 1 to 10.

[0108] To demonstrate the technical achievements of this solution, MATLAB / Simulink simulations were performed. Figure 2 This is the main circuit topology diagram of the grid-connected inverter in the above embodiments and simulations. Figure 2 As can be seen, this topology includes a DC-side power supply U. dc Three-phase full-bridge inverter circuit, filter inductor L f Filter capacitor C f Grid impedance L g and three-phase power grid E g A three-phase full-bridge inverter circuit is connected in series with the DC power supply U. dc and filter inductor L f Between, the filter capacitor C f Connected in parallel to the filter inductor L f Equivalent inductance L of grid connection g Between, the grid-connected equivalent inductance L g Connect to three-phase power grid E g Grid connection achieved. Among them, U... dc =770V, L f =0.9mH, C f =11.6uF, E g The amplitude is 311V.

[0109] Figure 3 The power input and response waveforms of the control scheme of this invention are without the input of the control scheme when the grid impedance is 15mH. Figure 4 The power input and response waveforms of the control scheme of this invention are applied when the grid impedance is 15mH. Figure 5The power input and response waveforms of the control scheme of this invention are without the input of the control scheme when the grid impedance is 4mH. Figure 6 The power input and response waveforms of the control scheme of this invention are applied when the grid impedance is 4mH. Figure 3 , Figure 4 , Figure 5 ,and Figure 6 The horizontal axis represents time, and the vertical axis represents power amplitude.

[0110] like Figure 3 As shown, the grid impedance L g =15mH, without the control scheme of this invention, the power response time is 1.72s; such as Figure 4 As shown, the grid impedance L g =15mH, after incorporating the control scheme of this invention, the power response time is 0.12s; as Figure 5 As shown, the grid impedance L g =4mH, without the control scheme of this invention, the power response time is 0.45s; such as Figure 6 As shown, the grid impedance L g =4mH, and after incorporating the control scheme of this invention, the power response time is 0.07s.

[0111] The circuit topology and control method of the present invention described above can be viewed as a hardware embodiment of the circuit topology alone, a software embodiment of only the control method, or an embodiment of a hardware-software combined control system based on the circuit topology and control method. Furthermore, the control method portion of the present invention can be implemented on one or more computer-usable storage media (including but not limited to disk storage, CD-ROM, optical storage, etc.) containing computer-usable program code, appearing in the form of a computer program product; and can be implemented using various computer languages, such as the object-oriented programming language Java and the interpreted scripting language JavaScript.

[0112] Furthermore, embodiments of the present invention are described in conjunction with flowcharts and / or block diagrams, and should be understood to mean that each block of the flowcharts and / or block diagrams, and combinations of blocks in the flowcharts and / or block diagrams, can be implemented by computer program instructions. These computer program instructions can be provided to a processor of a general-purpose computer, special-purpose computer, embedded processor, or other programmable data processing apparatus to produce a machine, such that the instructions, which execute via the processor of the computer or other programmable data processing apparatus, generate instructions for implementing the flowcharts of the present invention. Figure 1 One or more processes and / or boxes Figure 1apparatus for performing the functions specified in the block or blocks. These computer program instructions can also be stored in a computer-readable memory that can direct a computer or other programmable data processing apparatus to function in a particular manner, such that the instructions stored in the computer-readable memory produce an article of manufacture including instructions which implement the flow Figure 1 of the present application Figure 1 of the present application Figure 1 of the present application Figure 1 of the present application

[0113] Therefore, the above merely describes preferred embodiments of the present application and is not intended to limit the present application. Changes and modifications made by those skilled in the art based on the present application and the above description should be considered as equivalent solutions within the scope of the present application, and should fall within the protection scope of the present application.

Claims

1. A method of inverter power control, characterized by, The method comprises the following steps: Step 1, setting a given active power command signal , a given reactive power command signal , injecting a first-order step disturbance signal into the set given active power command signal at the same time interval , obtaining an active input power command signal and a reactive input power command signal ; Step 2, sample output grid-connected three-phase current , , and point of common coupling three-phase voltage , , , output grid-connected current obtained through transformation from three-phase stationary coordinate system to two-phase stationary coordinate system axis component , and point of common coupling voltage axis component , ; and output grid-connected current obtained through transformation from three-phase stationary coordinate system to two-phase rotating coordinate system axis component , and point of common coupling voltage axis component , ; Step 3, by grid current Axis component , And point of common coupling voltage Axis component , The active power signal And the reactive power signal Are calculated, and the active grid power And the reactive grid power Are obtained by low-pass filter Step 4, when the active grid-connected power is greater than the active input power command signal by an absolute value less than or equal to a set multiple, a step disturbance signal is recorded and the count is ended; Step 5, the count value T is modified by a coefficient to obtain a given power instruction feedforward coefficient ; Step 6, frequency signal from feed forward coefficient , reactive input power command signal and power fast control equation and shaft voltage command signal ; The expression of the power fast control equation is: In the formula, is the system rated angular frequency, is the rated line voltage amplitude, is the time constant of the given power feedforward low-pass filter, s is the Laplace operator, m is the active droop coefficient, and n is the reactive droop coefficient. Step 7, angle signal from frequency signal and integral control ; Step 8, given axis voltage command signal , through the common coupling point voltage axis component , and voltage closed-loop control equation to get current command signal axis component , ; Step 9, the inverter control signals are obtained by , , output grid current axis component , and current closed-loop control equation axis component , ; Step 10, to , The inverter control signals in the three-phase stationary coordinate system are obtained through the transformation equation of the two-phase rotating coordinate system to the three-phase stationary coordinate system , , .

2. The method of claim 1, wherein, the active input power command signal of step 1 and the reactive input power command signal are calculated as follows: 。 3. The method of claim 1, wherein, the active power signal of step 3 and the reactive power signal are calculated as 。 4. The method of claim 1, wherein, In step 4: The set multiple of 0.

1.

5. The method of claim 1, wherein, Step 5 the given power instruction feedforward coefficient The solving process is as follows: First, after the counting is completed, the step disturbance signal is set to zero, and then the given power command feedforward coefficient is set as follows In the formula, is a given correction factor.

6. The method of claim 1, wherein, The angle signal of step 7 The expression is: In the formula, s is a Laplace operator.

7. The method of claim 1, wherein, The expression of the voltage closed-loop control equation in step 8 is: wherein is a proportional coefficient of a voltage closed-loop control PI regulator, is an integral coefficient of a voltage closed-loop control PI regulator, s is a Laplace operator.

8. The method of claim 1, wherein, The expression of the current closed-loop control equation in step 9 is: wherein is a proportional coefficient of a current closed-loop control PI regulator, is an integral coefficient of a current closed-loop control PI regulator, s is a Laplace operator.

9. The method of claim 1, wherein, The expression of the inverter control signal in step 10 is: 。 10. An inverter power control system characterized by, comprise: A three-phase full-bridge inverter circuit is connected in series with a DC side power supply and a filter inductor , a filter capacitor is connected in parallel with the filter inductor and a grid equivalent inductor , the grid equivalent inductor is connected to a three-phase power grid , and a grid-connected inverter main circuit topology is formed For a given active power command signal Injecting a first order step disturbance signal Disturbance module Sampling output module for sampling output grid-connected three-phase current , , and public coupling point three-phase voltage , , sampling output module For obtaining output grid current Axis component , And point of common coupling voltage Axis component , Coordinate system transformation module for obtaining output grid current Axis component , And point of common coupling voltage Axis component , Coordinate system transformation module A computing module for calculating an active power signal and a reactive power signal ​ Low pass filter module for obtaining active and reactive grid power ​​ For recording active grid-connected power The difference between the active input power instruction signal The absolute value of the difference between the active input power instruction signal The count module a module for modifying the count value T by a coefficient to obtain a given power command feedforward coefficient of the modification module For obtaining a frequency signal by a power fast control equation and An axis voltage command signal A calculation module A computing module for obtaining an angle signal from a frequency signal and an integral control ​ for a given axis voltage command signal voltage command signal input module; and the current command signal is obtained by a voltage closed loop control equation axial component , calculation module Method for obtaining inverter control signals by means of a current closed loop control equation axial component , calculation module For converting , Inverter control signals are obtained by coordinate system transformation , , Coordinate system transformation module and a microprocessor and a memory, each of the modules, the microprocessor being programmed or configured to perform the steps of the inverter power control method of any one of claims 1-9.

11. A computer-readable storage medium, characterized in that, The computer readable storage medium stores a computer program programmed or configured to perform the inverter power control method of any one of claims 1-9.

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