Dual-band achromatic beam scanning antenna and antenna group array using the same

Abstract

The application relates to the field of microwave antennas, discloses a dual-band achromatic beam scanning antenna and an antenna array applying the same, the dual-band achromatic beam scanning antenna comprises a base, a dual-band feed source arranged in the base, a double-layer hollow rotating mechanism arranged on the base and two metasurface panels arranged in the double-layer hollow rotating mechanism, the metasurface panel comprises a double-channel beam deflection layer and a double-channel dispersion compensation layer. The antenna array comprises a plurality of the above beam scanning antennas. The application can deflect dual-band electromagnetic waves through the double-channel beam deflection layer in the metasurface panel, and can achromatize the dual-band electromagnetic waves through the double-channel dispersion compensation layer in the metasurface panel, the double-layer hollow rotating mechanism drives the two metasurface panels to rotate, the elevation and azimuth of the dual-band electromagnetic waves can be adjusted, so that the beam scanning antenna has the characteristics of low profile, low weight, low cost and strong adaptability.

Description

Technical Field

[0001] This application relates to the field of microwave antennas, and in particular to a dual-band chromatic aberration beam scanning antenna and antenna arrays for its applications. Background Technology

[0002] The beam scanning capability of low-profile planar antennas is an essential functional requirement in the fields of radar and communications, which is further divided into various specific requirements, such as beam scanning range, beam scanning speed, beam pointing accuracy, beamwidth, operating bandwidth, and multi-band coplanarity, etc.

[0003] For planar antenna beam-scanning antennas, among the aforementioned specifications, a large instantaneous bandwidth is a difficult requirement to achieve, often realized through real-time delay of the subarray in a phased array system. Although phased arrays have unparalleled advantages in beam scanning speed, for systems with low scanning speed requirements, the solution of adding subarrays to the phased array introduces extremely complex electronic control systems and high manufacturing costs.

[0004] Therefore, it is an urgent need to design and manufacture an antenna system that incorporates as many of the aforementioned functions as possible, such as beam scanning range, beam scanning speed, beam pointing accuracy, beamwidth, operating bandwidth, and multi-band coplanarity, while also possessing low profile, low weight, low cost, and strong adaptability. Summary of the Invention

[0005] In order to improve the limitations and incompatibility of planar antennas in terms of overall performance, this application provides a dual-band colorless beam scanning antenna and an antenna array for its application.

[0006] This application provides a dual-band colorless beam scanning antenna and its application antenna array, which adopts the following technical solution:

[0007] A dual-band achromatic beam scanning antenna includes a base, a dual-band feed source, a double-layer hollow rotating mechanism, and two metasurface plates. The dual-band feed source is disposed inside the base, and the double-layer hollow rotating mechanism is disposed on the base. The two dual-band feed sources are respectively disposed at the two hollow rotating ends of the double-layer hollow rotating mechanism, and the metasurface plates are located above the dual-band feed sources. The metasurface plates include a dual-channel beam deflection layer for deflecting dual-band electromagnetic waves and a dual-channel dispersion compensation layer for achromatic correction of dual-band electromagnetic waves.

[0008] By adopting the above technical solution, the dual-frequency feed on the base emits dual-frequency electromagnetic waves. These waves are first deflected by the dual-channel beam deflection layer of the metasurface plate, and then achromatic by the dual-channel dispersion compensation layer of the metasurface plate. This deflection improves the bandwidth performance of the antenna during beam scanning. A double-layer hollow rotating mechanism drives the two metasurface plates to rotate, thereby adjusting the elevation and azimuth angles of the emitted dual-frequency electromagnetic waves. This configuration gives the beam scanning antenna characteristics such as low profile, low weight, low cost, and high adaptability.

[0009] Preferably, the dual-frequency feed includes a first power divider network layer, a second power divider network layer, and an antenna radiating layer. The antenna radiating layer contains a plurality of Ku radiating elements connected to the first power divider network layer and a plurality of Ka radiating elements connected to the second power divider network layer.

[0010] By adopting the above technical solution, the first power divider network layer works with the Ku radiating element to transmit low-frequency electromagnetic waves, and the second power divider network layer works with the Ka radiating element to transmit high-frequency electromagnetic waves. By using dual independent feed channels, the dual-frequency operating bandwidth of the beam-scanning antenna is realized and the radiation efficiency of the antenna is increased.

[0011] Preferably, the plurality of Ku radiating units and Ka radiating units are arranged in a nested configuration.

[0012] By adopting the above technical solution, the Ku radiating element and the Ka radiating element are arranged in a nested manner, thereby reducing the coupling interference between the two frequencies and improving the radiation efficiency of the beam scanning antenna.

[0013] Preferably, the dual-channel beam deflection layer includes at least two first metal unit layers, one of which has a coplanar first low-frequency transmission channel and a first high-frequency deflection channel, and the other of which has a coplanar first low-frequency deflection channel and a first high-frequency transmission channel.

[0014] By adopting the above technical solution, when dual-frequency electromagnetic waves pass through a rotating first metal unit layer, the low-frequency electromagnetic wave is transmitted through the first low-frequency transmission channel, and the high-frequency electromagnetic wave is deflected through the first high-frequency deflection channel. The transmitted low-frequency electromagnetic wave is then deflected again through the first low-frequency deflection channel of another rotating first metal unit layer, and the deflected high-frequency electromagnetic wave is then transmitted through the first high-frequency transmission channel of another first metal unit layer. This configuration allows both high-frequency and low-frequency electromagnetic waves to be deflected through the dual-channel beam deflection layer of the metasurface plate, reducing the production cost of the beam scanning antenna and making it less prone to interference between electromagnetic waves of different frequencies during deflection.

[0015] Preferably, the first low-frequency transmission channel corresponds to the first low-frequency deflection channel, and the first high-frequency deflection channel corresponds to the first high-frequency transmission channel.

[0016] By adopting the above technical solution, the low-frequency channel and the high-frequency channel in the two first metal unit layers correspond to each other, making the transmission and deflection effect of the dual-channel beam deflection layer better for dual-frequency electromagnetic waves.

[0017] Preferably, the dual-channel dispersion compensation layer includes at least one second metal unit layer, which is composed of multiple dual-channel subarrays arranged in combination. The dual-channel subarrays have a coplanar second low-frequency transmission channel and a second high-frequency transmission channel, and the transmission phases of the multiple dual-channel subarrays are distributed in an arithmetic sequence.

[0018] By adopting the above technical solution, dual-frequency electromagnetic waves are transmitted through the second low-frequency transmission channel and the second high-frequency transmission channel of the second metal unit layer. Furthermore, the transmission phases of multiple dual-channel subarrays are distributed sequentially according to an arithmetic sequence, thereby compensating for beams at different frequencies and achieving electromagnetic wave achromatic correction. This configuration, using a metasurface plate to achromaticly correct electromagnetic waves emitted at an oblique angle, is more cost-effective and efficient, thus improving the instantaneous bandwidth performance of the beam-scanning antenna during beam scanning.

[0019] Preferably, within the high-frequency bandwidth of adjacent dual-channel subarrays, the slope of the transmission phase with respect to frequency is arranged in an arithmetic sequence, and within the low-frequency bandwidth of adjacent dual-channel subarrays, the slope of the transmission phase with respect to frequency is arranged in an arithmetic sequence.

[0020] By adopting the above technical solution, after high-frequency electromagnetic waves and low-frequency electromagnetic waves pass through the second low-frequency transmission channel and the second high-frequency transmission channel of the dual-channel subarray, the color difference aberration effect of high-frequency electromagnetic waves and low-frequency electromagnetic waves is the same.

[0021] Preferably, the double-layer hollow rotating mechanism includes an upper outer ring, a support ring, a lower outer ring, and two driving units. The support ring is mounted on the base by a support member. The upper and lower outer rings are respectively rotatably sleeved on both sides of the support ring along the axial direction. Two metasurface plates are respectively disposed inside the upper and lower outer rings. The two driving units are disposed on the base and drive the upper and lower outer rings to rotate independently, respectively.

[0022] By adopting the above technical solution, the two drive units drive the upper and lower outer rings to rotate independently on the support ring, thereby driving the two metasurface plates to rotate independently, thus enabling adjustment of the elevation and azimuth angles of the emitted beam. This configuration eliminates the need for large counterweights, minimizing changes in the center of gravity and moment of inertia caused by component rotation, thereby significantly reducing the profile height and overall weight of the beam scanning antenna.

[0023] Preferably, the driving unit includes a driving motor and a driving gear, and gear rings that mesh with the driving gear are formed on the outer side walls of both the upper and lower outer rings.

[0024] By adopting the above technical solution, the drive motor drives the drive gear to rotate, and the drive gear drives the upper and lower outer rings to rotate through the gear rings on the outer sides of the upper and lower outer rings. This configuration, using the drive gear meshing with the gear rings to drive the upper and lower outer rings, makes the rotation of the metasurface plate faster and more precise.

[0025] An antenna array includes multiple beam scanning antennas. The base and support ring are configured as polygons of the same shape. The multiple beam scanning antennas are spliced ​​together to form an antenna array. The multiple polygonal bases are spliced ​​together, and the multiple polygonal support rings are spliced ​​together. One driving unit drives the upper outer ring of the multiple beam scanning antennas to rotate, and another driving unit drives the lower outer ring of the multiple beam scanning antennas to rotate.

[0026] By adopting the above technical solution, multiple beam scanning antennas are spliced ​​together to form an antenna array, creating an antenna array with an equivalent larger aperture, thereby improving the overall antenna gain and enhancing antenna communication efficiency. Multiple bases and support rings are spliced ​​together, making the antenna array structure more stable. A single drive unit drives multiple upper or lower outer rings to rotate, further reducing the production cost of the antenna array.

[0027] In summary, this application includes at least one of the following beneficial technical effects:

[0028] 1. By using a dual-channel beam deflection layer within a metasurface plate to deflect dual-frequency electromagnetic waves, and then using a dual-channel dispersion compensation layer within the metasurface plate to achromaticize the dual-frequency electromagnetic waves, while a double-layer hollow rotating mechanism drives the two metasurface plates to rotate, the elevation and azimuth angles of the emitted dual-frequency electromagnetic waves can be adjusted. This gives the beam scanning antenna characteristics such as low profile, low weight, low cost, and strong adaptability.

[0029] 2. By employing dual independent feeding channels within the dual-frequency feed source, the dual-frequency operating bandwidth of the beam-scanning antenna is achieved, and the antenna's radiation efficiency is increased;

[0030] 3. By employing a dual-channel beam deflection layer, dual-frequency electromagnetic waves are deflected by the dual-channel beam deflection layer of the metasurface plate. On the one hand, this reduces the production cost of the beam scanning antenna, and on the other hand, it makes it less likely for electromagnetic waves of different frequencies to interfere with each other during deflection.

[0031] 4. By employing a dual-channel dispersion compensation layer to achromaticize electromagnetic waves emitted at an oblique angle, the cost is lower and the efficiency is higher, and the instantaneous bandwidth performance of the beam scanning antenna in beam scanning is improved.

[0032] 5. By using multiple beam scanning antennas to splice and combine them into an antenna array, an antenna array with an equivalent larger aperture is formed, thereby improving the overall antenna gain and enhancing antenna communication efficiency. Attached Figure Description

[0033] Figure 1 This is a schematic diagram of the overall structure of the beam scanning antenna in Embodiment 1 of this application;

[0034] Figure 2 This is a partial structural schematic diagram of the beam scanning antenna in Embodiment 1 of this application;

[0035] Figure 3 This is a partial structural cross-sectional view of the beam scanning antenna in Embodiment 1 of this application;

[0036] Figure 4 This is a cross-sectional view of the dual-frequency feed of the beam scanning antenna in Embodiment 1 of this application;

[0037] Figure 5 This is an exploded view of the dual-frequency feed of the beam scanning antenna in Embodiment 1 of this application;

[0038] Figure 6 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the Ka radiating element and the Ka power divider network;

[0039] Figure 7 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the Ku radiating element and the Ku power divider network;

[0040] Figure 8 This is a cross-sectional view of the dual-channel beam deflection layer of the beam scanning antenna in Embodiment 1 of this application;

[0041] Figure 9 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting structure A in the first metal unit layer;

[0042] Figure 10 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting structure B in the first metal unit layer;

[0043] Figure 11 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting structure C in the first metal unit layer;

[0044] Figure 12 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting structure D in the first metal unit layer;

[0045] Figure 13This is a schematic diagram of the beam scanning antenna in Embodiment 1 of this application, which highlights the sequential rotation of the crystal axes of the low-frequency channel units in the low-biased high-transparency layer.

[0046] Figure 14 This is a schematic diagram of the beam scanning antenna in Embodiment 1 of this application, which highlights the sequential rotation of the crystal axes of the high-frequency channel units in the high-bias low-transparency layer;

[0047] Figure 15 This is a cross-sectional view of the dual-channel dispersion compensation layer of the beam scanning antenna in Embodiment 1 of this application;

[0048] Figure 16 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the second metal unit layer;

[0049] Figure 17 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the dual-channel subarray.

[0050] Figure 18 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the second subarray within structure E in the second metal unit layer;

[0051] Figure 19 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the third subarray within structure E of the second metal unit layer;

[0052] Figure 20 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the fourth subarray within structure E of the second metal unit layer;

[0053] Figure 21 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the fifth subarray within structure E of the second metal unit layer;

[0054] Figure 22 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the second subarray within structure F in the second metal unit layer;

[0055] Figure 23 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the third subarray within structure F in the second metal unit layer;

[0056] Figure 24 This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the fourth subarray within structure F in the second metal unit layer;

[0057] Figure 25This is a partial structural diagram of the beam scanning antenna in Embodiment 1 of this application, highlighting the fifth subarray within structure F in the second metal unit layer;

[0058] Figure 26 This is a schematic diagram of the overall structure of the antenna array in Embodiment 2 of this application.

[0059] Explanation of reference numerals in the attached drawings: 1. Base; 2. Dual-frequency feed; 21. First power divider network layer; 211. Ku power divider network; 22. Second power divider network layer; 221. Ka power divider network; 23. Antenna radiating layer; 231. Ku radiating element; 232. Ka radiating element; 3. Double-layer hollow rotating mechanism; 31. Upper outer ring; 32. Support ring; 33. Lower outer ring; 34. Drive unit; 341. Drive motor; 342. Drive gear; 4. Metasurface plate; 41. Dual-channel beam deflection layer; 411. First metal unit layer; 4111. First low-frequency transmission channel; 4112. First high-frequency deflection channel; 4113. First low-frequency deflection channel; 41 14. First high-frequency transmission channel; 42. Dual-channel dispersion compensation layer; 421. Second metal unit layer; 4211. Dual-channel subarray; 42111. Second low-frequency transmission channel; 42112. Second high-frequency transmission channel; 43. Low-biased high-transparency layer; 44. High-biased low-transparency layer; 5. First core board; 6. First through hole; 7. Second through hole; 8. Third through hole; 9. Gap; 10. Metal through hole; 11. Second core board; 12. First foam board; 13. Second foam board; 15. Third core board; 16. Third foam board; 17. Support component; 18. Ball bearing; 19. Circular track; 20. Track cover; 26. First metal base plate; 27. Second metal base plate. Detailed Implementation

[0060] The following is in conjunction with the appendix Figure 1-26 This application will be described in further detail.

[0061] This application discloses a dual-band chromatic aberration beam scanning antenna and its application in antenna arrays.

[0062] Example 1:

[0063] Reference Figure 1 and 3A dual-band aberration-free beam scanning antenna includes a base 1, a dual-band feed 2, a double-layer hollow rotating mechanism 3, and two metasurface plates 4. The base 1 is hexagonal, the dual-band feed 2 is circular and fixedly embedded in the center of the base 1, the double-layer hollow rotating mechanism 3 is mounted on the base 1, and the two metasurface plates 4 are respectively installed in the two hollow rotating ends of the double-layer hollow rotating mechanism 3. The two metasurface plates 4 are circular and located directly above and parallel to the dual-band feed 2. Each metasurface plate 4 includes a stacked dual-channel beam deflection layer 41 and a dual-channel dispersion compensation layer 42, with the dual-channel dispersion compensation layer 42 located below the dual-channel beam deflection layer 41, away from the dual-band feed 2.

[0064] The dual-frequency feed 2 emits dual-frequency electromagnetic waves, which sequentially pass through two rotating metasurface plates 4. The waves first pass through the dual-channel beam deflection layer 41 of the metasurface plate 4 and are deflected, then pass through the dual-channel dispersion compensation layer 42 for achromatic correction. This deflection of the dual-frequency electromagnetic waves improves the antenna's bandwidth performance during beam scanning. A double-layer hollow rotating mechanism 3 drives the two metasurface plates 4 to rotate, thereby adjusting the elevation and azimuth angles of the emitted dual-frequency electromagnetic waves. This results in a beam-scanning antenna with characteristics such as low profile, low weight, low cost, and high adaptability.

[0065] Reference Figure 1 and 2 Specifically, the double-layer hollow rotating mechanism 3 includes an upper outer ring 31, a support ring 32, a lower outer ring 33, and two driving parts 34. The outer contour of the support ring 32 is a regular hexagon and is the same as that of the base 1. The support ring 32 is fixedly installed on the base 1 by twelve support members 17. In this application, the base 1 and the support members 17 can both be made of high-hardness plastic, and the upper outer ring 31, the support ring 32, and the lower outer ring 33 can all be made of aluminum-magnesium alloy, thereby reducing the overall weight of the beam scanning antenna.

[0066] Reference Figure 3 The cross-section of the support ring 32 is a convex shape that protrudes outwards. The cross-sections of the upper outer ring 31 and the lower outer ring 33 are L-shaped. The upper outer ring 31 is fitted and coaxially rotated on the top wall of the support ring 32 along the axial direction of the support ring 32, and the lower outer ring 33 is fitted and coaxially rotated on the bottom wall of the support ring 32 along the axial direction of the support ring 32.

[0067] Reference Figure 1 , 2 Two metasurface plates 4 are embedded in the upper outer ring 31 and the lower outer ring 33. The inner diameter of the upper outer ring 31 and the lower outer ring 33 is 502mm, and the outer diameter of the metasurface plate 4 is 500mm. There is a 2mm gap between the metasurface plate 4 and the upper outer ring 31 and the lower outer ring 33, so that the metasurface plate 4 is not easily damaged by bumps.

[0068] The spacing between the two metasurface plates 4 is 25mm, and the spacing between the lower metasurface plate 4 and the dual-frequency feed 2 is 35mm. The spacing of 25mm and 35mm is sufficient to convert the local electromagnetic field of the Ku band emitted by the dual-frequency feed 2 and the metasurface plate 4 into a plane wave, thus ensuring that there is no local field coupling between the two metasurface plates 4 and the dual-frequency feed 2, thereby improving the antenna efficiency.

[0069] Annular tracks 19 are provided between the upper outer ring 31 and the support ring 32, and between the lower outer ring 33 and the support ring 32. Multiple ball bearings 18 are rolled within the annular tracks 19. The annular tracks 19, in conjunction with the ball bearings 18, allow the upper outer ring 31 and the lower outer ring 33 to rotate freely on the support ring 32. Two track covers 20 are detachably fixed to the inner wall of the support ring 32 by bolts. Opening the two track covers 20 allows the ball bearings 18 to be inserted into the two annular tracks 19.

[0070] The drive unit 34 includes a drive motor 341 and a drive gear 342. The drive motor 341 is fixedly mounted on the base 1. The drive end of one drive motor 341 is located below the support ring 32, and the drive end of the other drive motor 341 passes through the support ring 32 and is located above the support ring 32. The drive gear 342 is fixedly mounted on the drive end of the drive motor 341.

[0071] Gear rings are formed on the outer walls of both the upper outer ring 31 and the lower outer ring 33, and two drive gears 342 mesh with the two gear rings respectively. In this application, the drive motor 341 can be a servo motor. The drive motor 341 drives the upper outer ring 31 and the lower outer ring 33 to rotate independently through the drive gears 342 and the gear rings. By using the drive gears 342 to mesh with the gear rings to drive the upper outer ring 31 and the lower outer ring 33, the rotation of the metasurface plate 4 becomes faster and more precise.

[0072] Two independently rotating metasurface plates 4, by adjusting their rotation angles individually, allow normally incident electromagnetic waves to be deflected to the desired direction after passing through the combined metasurface plates 4. When the dual-frequency feed 2 is placed horizontally, a two-dimensional coordinate system is established with the horizontal direction as the x-axis and y-axis. The x-axis direction is taken as the initial angle of the sum of the rotation angles of the two metasurface plates 4. Since the metasurface plates 4 can rotate horizontally in the xy-plane, the angle of the sum ranges from 0 to 360°. Therefore, the maximum beam deflection angle of the antenna system under the combined effect of the two metasurface plates 4 can be determined to be θ. max At this point, the relationships between the rotation angles ω1 and ω2 and the azimuth and elevation angles of the beam are as follows:

[0073]

[0074] Where Δω=(ω2-ω1) / 2, therefore ω2>ω1 is set. Based on the above formula, the relationship between the beam deflection angle and the rotation angle of the two metasurface plates 4 can be obtained. The two drive motors 341 are respectively connected to their respective power lines and external computer control lines. Through pre-programmed software on the computer, the drive motors 341 are controlled to rotate as required, thereby controlling the beam direction.

[0075] Reference Figure 4 and 5 Specifically, the dual-band feed 2 includes a first power divider network layer 21, a second power divider network layer 22, and an antenna radiating layer 23 stacked from bottom to top. The first power divider network layer 21 includes a first core board 5 and a Ku power divider network 211 located on the bottom wall of the first core board 5; the second power divider network layer 22 includes two first core boards 5 and a Ka power divider network 221 located between the two first core boards 5; the antenna radiating layer 23 includes a first core board 5 and multiple Ku radiating elements 231 and Ka radiating elements 232 located on the top wall of the first core board 5. The Ku radiating elements 231 and Ka radiating elements 232 are arranged on the same plane, and the Ku radiating elements 231 are connected to the Ku power divider network 211, and the Ka radiating elements 232 are connected to the Ka power divider network 221.

[0076] The dual-band feed 2 transmits dual-band electromagnetic waves as a flat panel antenna. The input port of the Ka power splitter network 221 is an SMA connector, and the RF back-end is connected to the Ka power splitter network 221 through an SMA connector. The frequency range of the Ka band is 19.6GHz-21.2GHz. The input port of the Ku power splitter network 211 is an SMA connector, and the RF back-end is connected to the Ku power splitter network 211 through an SMA connector. The frequency range of the Ku band is 12.25GHz-12.75GHz.

[0077] Ka power divider 221 works with Ka radiating element 232 to transmit high-frequency electromagnetic waves, while Ku power divider 211 works with Ku radiating element 231 to transmit low-frequency electromagnetic waves. Using dual independent feed channels, the planar antenna achieves dual-frequency operating bandwidth and increases its radiation efficiency. The co-plane arrangement of Ku radiating element 231 and Ka radiating element 232 makes the planar antenna thinner and lighter.

[0078] The dual-frequency feed 2 provides a PCB first core board 5 consisting of five copper metal layers and four loss tangents of 0.0009. The five copper metal layers, from top to bottom, are an antenna radiating layer 23, a first metal base plate 26, a Ka power divider network 221, a second metal base plate 27, and a Ku power divider network 211. The four first core boards 5 are distributed between the five copper metal layers.

[0079] In the fabrication of the dual-frequency feed 2, a three-step pressing and three-through-hole process is adopted: 1. A first through-hole 6 is formed on a first core plate 5 with a first metal base plate 26 as the top wall and a Ka power divider network 221 as the bottom wall. A copper layer is electroplated on the hole wall of the first through-hole 6 to electrically connect the first metal base plate 26 and the Ka power divider network 221; 2. The first core plate 5 with a second metal base plate 27 as the bottom wall is pressed onto the bottom wall of the first core plate 5 with the Ka power divider network 221 as the bottom wall. A second through-hole 7 is formed on the two first core plates 5. A copper layer is electroplated on the hole wall of the second through-hole 7 to form A copper layer is applied to electrically connect the first metal base plate 26 and the second metal base plate 27. 3. The first metal top plate, with its top wall being the antenna radiating layer 23, is pressed onto the top wall of the first core plate 5, which has its top wall being the first metal base plate 26. The first core plate 5, with its bottom wall being the Ku power divider network 211, is pressed onto the bottom wall of the first core plate 5, which has its bottom wall being the second metal base plate 27. Third through holes 8 are formed on the four first core plates 5, and a copper layer is electroplated on the hole walls of the third through holes 8, electrically connecting the Ku power divider network 211 to the Ku radiating elements 231 within the antenna radiating layer 23. Furthermore, PP prepreg sheets are placed between each pair of adjacent first core plates 5 for bonding and reinforcement, resulting in higher structural strength for the dual-frequency feed 2.

[0080] Reference Figure 5 , 6 In the configuration of 7, every four adjacent Ku radiating elements 231 form a square grid, and the square grid surrounds the periphery of a Ka radiating element 232; every four adjacent radiating elements form a square grid, and the square grid surrounds the periphery of a Ku radiating element 231. The Ku radiating elements 231 and Ka radiating elements 232 are arranged in a nested quadrilateral grid pattern, and the two sets of grids are separated by a metal wire connecting the first core plate 5, thereby reducing the coupling interference between the two frequencies and improving the radiation efficiency of the flat panel antenna.

[0081] Both independent feed networks are unequal-division feed networks used to match the outline of the circular dual-band feed 2. The unequal-division feed network ensures that the antenna's radiating aperture can occupy the area of ​​the circular dual-band feed 2 to the maximum extent, thereby improving antenna efficiency. The unequal-division feed networks for the Ku and Ka bands are the same in terms of unequal division. The process from the main feed port into the quarter-circular dual-band feed 2 is an equal division process. Then, a three-order unequal division process begins within the quarter-circular dual-band feed 2: The first order is an 8:7 ratio, with the 8-percentage branch being divided three times and fed to the 2*2 radiating element for radiation. The 7-percentage branch undergoes a second unequal division feed. The second order is a 4:3 ratio, with the 4-percentage branch being divided twice and the 3-percentage branch undergoing a third unequal feed. The third order is a 2:1 ratio, with the three portions of energy (3-percentage) fed into the 2*2 radiating element. At this point, all elements across the entire area are fed with equal amplitude and equal phase.

[0082] The Ku radiating element 231 adopts a cross-shaped structure and is electrically connected to the Ku power divider network 211 through the third through-hole 8, thereby emitting low-frequency electromagnetic waves. Adjacent Ku radiating elements 231 are arranged with a 90° geometric rotation, and the Ku power divider network 211 is finely adjusted in microstrip line length to achieve equal phase difference feeding at 90°, thus realizing Ku-band radiation with excellent circular polarization axial ratio.

[0083] Ka radiating element 232 adopts an octagonal structure, facilitating maximum nesting with the cross-shaped structure of Ku radiating element 231. Multiple C-shaped slots 9 are formed on the first metal base plate 26 corresponding to the multiple Ka radiating elements 232, and multiple metal through holes 10 are formed on the periphery of each slot 9. Ka power divider network 221 is electrically connected to the first metal base plate 26 through a third through hole 8. The first metal base plate 26 is coupled to the Ka radiating elements 232 through the slots 9 and the metal through holes 10, thereby emitting high-frequency electromagnetic waves. Ka-band feeding uses slot 9 coupling to maximize the operating bandwidth and further optimize the axial ratio of the radiated electromagnetic waves.

[0084] Reference Figure 4 Of the four first core boards 5, the three with attached power divider networks are all 0.254 mm thick, while the first core board 5 with attached antenna radiating layer 23 is 1.516 mm thick. Additionally, the PP prepreg is 0.1 mm thick, the copper foil is 35 μm thick, and the diameter of the dual-frequency feed 2 is 500 mm. Thus, the overall thickness of the dual-frequency feed 2 is within 2.4 mm, making the antenna thinner and lighter.

[0085] Reference Figure 8 Specifically, the dual-channel beam deflection layer 41 includes a low-bias high-transmittance layer 43 and a high-bias low-transmittance layer 44 with the same layer structure stacked on top of each other. A first foam board 12 is placed between the low-bias high-transmittance layer 43 and the high-bias low-transmittance layer 44. A layer of cyanate ester film is laid on both sides of the first foam board 12 to bond and reinforce the low-bias high-transmittance layer 43 and the high-bias low-transmittance layer 44. The low-bias high-transmittance layer 43 is located below the high-bias low-transmittance layer 44. The layer structure of both the low-bias high-transmittance layer 43 and the high-bias low-transmittance layer 44 consists of four layers of first metal unit layer 411, three second core boards 11 and two second foam boards 13.

[0086] In the low-to-high-transparency layer 43 or the high-to-low-transparency layer 44, two second foam boards 13 are sequentially located between three second core boards 11. Two first metal unit layers 411 are symmetrically located on the upper and lower surfaces of the middle second core board 11 in the low-to-high-transparency layer 43 or the high-to-low-transparency layer 44. Two first metal unit layers 411 are symmetrically located on the surfaces of the upper and lower second core boards 11 in the low-to-high-transparency layer 43 or the high-to-low-transparency layer 44 that are far apart from each other. The dual-channel beam deflection layer 41 is made by a pressing process. The first metal unit layer 411 is made by copper foil printing. A layer of cyanate ester film is laid on both sides of each second foam board 13 to bond and reinforce the three second core boards 11, making the dual-channel beam deflection layer 41 structurally stronger.

[0087] Reference Figure 9 and 11 In the low-bias, high-transmittance layer 43, coplanar, approximately circular, first low-frequency anisotropic units and approximately triangular, first high-frequency isotropic units are formed within the first metal unit layer 411. The first low-frequency anisotropic units serve as first low-frequency deflection channels 4113, causing the low-frequency electromagnetic wave beam to be deflected upon rotation; the first high-frequency isotropic units serve as first high-frequency transmission channels 4114, causing the high-frequency electromagnetic wave beam to be transmitted upon passage.

[0088] The first metal unit layers 411 on both surfaces of the second core plate 11 located in the middle of the low-biased high-transparency layer 43 have the same shape and are referred to as structure A. The first metal unit layers 411 on the surfaces of the two second core plates 11 located on opposite sides of the low-biased high-transparency layer 43 have the same shape and are referred to as structure B. The dimensions of the first low-frequency anisotropic unit and the first high-frequency isotropic unit in structures A and B have slight differences in the X-axis and Y-axis, thereby enabling beam deflection of low-frequency signals.

[0089] Reference Figure 10 and 12 In the high-bias, low-transmittance layer 44, coplanar approximately hexagonal first low-frequency isotropic units and approximately elliptical first high-frequency anisotropic units are formed within the first metal unit layer 411. The first low-frequency isotropic units serve as first low-frequency transmission channels 4111, allowing low-frequency electromagnetic wave beams to be transmitted after passing through them; the first high-frequency anisotropic units serve as first high-frequency deflection channels 4112, and deflect high-frequency electromagnetic wave beams after rotation.

[0090] The first metal unit layers 411 on both surfaces of the second core plate 11 located in the middle of the high-bias-low-transparency layer 44 have the same shape and are denoted as structure C. The first metal unit layers 411 on the surfaces of the two second core plates 11 located on opposite sides of the high-bias-low-transparency layer 44 have the same shape and are denoted as structure D. The dimensions of the first high-frequency anisotropic unit and the first low-frequency isotropic unit in structure C and structure D have slight differences in the X-axis and Y-axis, thereby enabling beam deflection of high-frequency signals.

[0091] Reference Figure 9 and 10 In the high-bias low-transparency layer 44 and the low-bias high-transparency layer 43, multiple first low-frequency transmission channels 4111 correspond one-to-one with multiple first low-frequency deflection channels 4113, and multiple first high-frequency deflection channels 4112 correspond one-to-one with multiple first high-frequency transmission channels 4114, so that the dual-channel beam deflection layer 41 has a better transmission and deflection effect on dual-frequency electromagnetic waves.

[0092] Reference Figure 8 When dual-frequency electromagnetic waves pass sequentially through the rotating low-bias high-transparency layer 43 and the high-bias low-transparency layer 44 with dual channels, both frequencies of electromagnetic waves are deflected. This reduces the production cost of the beam scanning antenna and makes it less likely for electromagnetic waves of different frequencies to interfere with each other during deflection.

[0093] Reference Figure 13 and 14 Anomalous deflection and transmission of incident electromagnetic waves can only be achieved when the crystal axes of adjacent anisotropic units rotate. In the low-frequency channel of the low-biased high-transparency layer 43, the angle between the crystal axes of adjacent units is 31°, while in the high-frequency channel of the high-biased low-transparency layer 44, the angle between the crystal axes of adjacent units is 50°. In this way, both high-frequency and low-frequency electromagnetic waves can have the same deflection angle.

[0094] In summary, the dual-channel beam deflection layer 41 in the metasurface plate 4 achieves a transmittance of 94% for normally incident circularly polarized electromagnetic waves in the Ku band within the entire frequency band of 12.25-12.75GHz, and a transmittance of 91% in the Ka band within the range of 19.6-21.2GHz. Furthermore, the deflection angle of the transmitted waves in both frequency bands is the design value of 22.5°.

[0095] Reference Figure 8 The second core board 11 is a PCB core board with a thickness of 0.508 mm, a node constant of 2.55, and a loss tangent of 0.0013. Its interior is a mixture of multi-layer fiberglass cloth, polytetrafluoroethylene, and ceramic filler. The first metal unit layer 411 is a copper layer with a thickness of 0.035 mm. The first foam board 12 is a PMI foam board with a thickness of 5 mm. The second foam board 13 is a PMI foam board with a thickness of 2 mm. The thickness of the dual-channel beam deflection layer 41 is 16 mm, which makes the metasurface plate 4 thinner and lighter.

[0096] Reference Figure 15 Specifically, the dual-channel dispersion compensation layer 42 includes four second metal unit layers 421, four third core boards 15, and three third foam boards 16. The four second metal unit layers 421 are respectively located on the four third core boards 15, and the three third foam boards 16 are respectively located between the four third core boards 15. The third foam boards 16 separate and protect the third core boards 15, making the second metal unit layers 421 on the third core boards 15 less susceptible to damage. The cyanate ester film bonds and reinforces the third foam boards 16 with the third core boards 15, resulting in higher structural strength of the dual-channel dispersion compensation layer 42.

[0097] Reference Figure 16 and 17 The second metal unit layer 421 is composed of five dual-channel subarrays 4211 arranged sequentially. The five dual-channel subarrays 4211 are referred to as subarray 1, subarray 2, subarray 3, subarray 4, and subarray 5, respectively. The width of each dual-channel subarray 4211 is 100 mm. Each dual-channel subarray 4211 contains a coplanar second low-frequency transmission channel 42111 and a second high-frequency transmission channel 42112, and the transmission phases of the five dual-channel subarrays 4211 are distributed in an arithmetic sequence.

[0098] The dual-channel subarray 4211 is composed of multiple approximately circular second low-frequency isotropic units and multiple approximately triangular second high-frequency isotropic units, all coplanar. The second low-frequency isotropic units serve as second low-frequency transmission channels 42111, allowing low-frequency electromagnetic wave beams to be transmitted. The second high-frequency isotropic units serve as second high-frequency transmission channels 42112, allowing high-frequency electromagnetic wave beams to be transmitted. The nested arrangement of these units minimizes interference between high- and low-frequency electromagnetic waves.

[0099] The transmission phases of the five dual-channel subarrays 4211 are distributed sequentially according to an arithmetic progression. Subarray 1 serves as the starting subarray, using an exposed third core plate 15 instead of a metal pattern. The transmission phase slope of subarray 1 is then used as a reference base, with subarrays 2, 3, 4, and 5 increasing in-band transmission phase slopes in an arithmetic progression. The transmission phase slopes of the five dual-channel subarrays 4211 are 0, 13.78, 27.56, 41.33, and 55.11 (° / GHz), satisfying the subarray phase slope distribution requirements of the slope expression at a beam deflection angle of 22.5°. Perfect in-band and interband dispersion compensation is then performed on the metasurface at this deflection angle.

[0100] Reference Figure 17In the second metal unit layer 421, there are multiple gaps between the second high-frequency isotropic unit and the second low-frequency isotropic unit. As the sequence number of the dual-channel subarray 4211 increases, the duty cycle of the metal region in the second metal unit layer 421 increases, while the duty cycle of the gaps in the second metal unit layer 421 decreases. By reducing the gaps in the metal pattern, the near-field coupling phenomenon of the electromagnetic field is increased, the frequency range of the passband is compressed, thereby improving the slope value of the transmission phase as a function of frequency within the dual-frequency bandwidth.

[0101] Reference Figure 15 and Figure 18-25 As the serial number of the dual-channel subarray 4211 increases, the slope value of the transmission phase change with frequency within the dual-band bandwidth continuously increases. By compensating for beams at different frequency points through the continuously increasing slope value within the dual-band bandwidth, electromagnetic wave achromatic correction is achieved. Using the dual-channel dispersion compensation layer 42 to achromaticly correct dual-band electromagnetic waves emitted at an oblique angle is more cost-effective and efficient, thereby improving the instantaneous bandwidth performance of the flat panel antenna in beam scanning.

[0102] The second metal unit layers 421 on the surfaces of the two third core plates 15 located in the middle of the dual-channel dispersion compensation layer 42, which are far apart from each other, have the same shape and are denoted as structure E. The second metal unit layers 421 on the upper and lower sides of the dual-channel dispersion compensation layer 42, which are far apart from each other, have the same shape and are denoted as structure F. There are slight differences in the size of the second high-frequency isotropic unit and the second low-frequency isotropic unit in structure E and structure F, which can improve the transmittance of high-frequency electromagnetic waves and low-frequency electromagnetic waves.

[0103] For normally incident electromagnetic waves in the Ku band, the dual-channel dispersion compensation layer 42 achieves an average transmittance of 96% in the entire band (12.25-12.75GHz) and an average transmittance of 92% in the Ka band (19.6-21.2GHz). Furthermore, the transmission phase slopes in the Ku and Ka bands are distributed in an arithmetic sequence according to the serial numbers of the dual-channel subarray 4211.

[0104] Reference Figure 15 The third core board 15 is a PCB core board with a thickness of 0.508 mm, a node constant of 2.55, and a loss tangent of 0.0013. Its interior is a mixture of multi-layer fiberglass cloth, polytetrafluoroethylene, and ceramic filler. The second metal unit layer 421 is formed by etching copper foil with a thickness of 0.035 mm. The three third foam boards 16 are all PMI foam boards with a density of 0.11 g / cm3, and the thicknesses of the three third foam boards 16 are 3.9 mm, 2.6 mm, and 3.9 mm, respectively. The thickness of the cyanate ester adhesive layer is 0.106 mm. The thickness of the dual-channel dispersion compensation layer 42 is 13.4 mm, which makes the metasurface plate 4 thinner and lighter.

[0105] Reference Figure 8 and 15 After the dual-channel dispersion compensation layer 42 and the dual-channel beam deflection layer 41 are combined, the working mechanism of the dual-channel dual-band beam deflection achromatic is as follows (the working mechanism of low frequency and high frequency is the same): First, the incident electromagnetic wave first passes through the dual-channel dispersion compensation layer 42, and the phase compensation in the band is performed by using the arithmetic distribution of the phase slope of the dual-channel subarray 4211, and the phase requirements of the array surface for in-band achromatic are reserved; Second, the electromagnetic wave passes through the beam deflection metasurface, and the transmission phase difference in each subarray is made into a gradient phase distribution. Combined with the subarray phase distribution of the entire array surface, perfect achromatic achromatic between and within the dual-band bands can be achieved.

[0106] The implementation principle of Embodiment 1 of this application is as follows: The dual-frequency feed 2 can emit dual-frequency electromagnetic waves, which pass sequentially through two metasurface plates 4. The dual-frequency electromagnetic waves first pass through the dual-channel beam deflection layer 41 of the metasurface plate 4, and then through the dual-channel dispersion compensation layer 42. When the dual-frequency electromagnetic waves pass through the dual-channel beam deflection layer 41, they are deflected. When the dual-frequency electromagnetic waves pass through the dual-channel dispersion compensation layer 42, they undergo achromatic correction, which not only allows the dual-frequency electromagnetic waves to be deflected, but also improves the bandwidth performance of the antenna in beam scanning. A double-layer hollow rotating mechanism 3 is used to drive the two metasurface plates 4 to rotate, thereby adjusting the elevation and azimuth angles of the emitted dual-frequency electromagnetic waves. In this way, the beam scanning antenna has the characteristics of low profile, low weight, low cost, and strong adaptability.

[0107] Example 2:

[0108] Reference Figure 26 This application discloses an antenna array comprising at least three dual-band chromatic aberration-free beam scanning antennas, wherein every three beam scanning antennas form a triangular grid and are spliced ​​together to form an antenna array. By splicing the base 1 and support ring 32 of the three beam scanning antennas, the splicing of the three beam scanning antennas can be quickly completed, and the splicing of the three bases 1 and support ring 32 makes the antenna array structure more stable.

[0109] At this time, the drive gear 342 of one drive unit 34 simultaneously engages the gear rings of three upper outer rings 31 in one triangular grid, and the drive gear 342 of one drive unit 34 simultaneously engages the gear rings of three lower outer rings 33 in another adjacent triangular grid. One drive unit 34 can simultaneously drive multiple upper outer rings 31 or lower outer rings 33 to rotate, thereby further reducing the production cost of the antenna array.

[0110] One drive unit 34 can drive three metasurface plates 4 to rotate synchronously. Therefore, all three sub-antennas of the antenna array point in the same direction, and the antenna array improves the gain by 4.5dB compared to a single antenna.

[0111] The implementation principle of Embodiment 2 of this application is as follows: multiple beam scanning antennas are spliced ​​together to form an antenna array, forming an antenna array with an equivalent larger aperture, thereby improving the overall antenna gain and enhancing the antenna communication efficiency.

[0112] The above are all preferred embodiments of this application, and are not intended to limit the scope of protection of this application. Therefore, all equivalent changes made in accordance with the structure, shape and principle of this application should be covered within the scope of protection of this application.

Claims

1. A dual-band chromatic aberration-free beam scanning antenna, characterized in that: The device includes a base (1), a dual-frequency feed (2), a double-layer hollow rotating mechanism (3), and two metasurface plates (4). The dual-frequency feed (2) is located inside the base (1), the double-layer hollow rotating mechanism (3) is located on the base (1), and the two metasurface plates (4) are respectively located at the two hollow rotating ends of the double-layer hollow rotating mechanism (3). The metasurface plates (4) are located above the dual-frequency feed (2). The metasurface plates (4) include a dual-channel beam deflection layer (41) for deflecting dual-frequency electromagnetic waves and a dual-channel dispersion compensation layer (42) for achromatic correction of dual-frequency electromagnetic waves. The dual-channel beam deflection layer (41) includes at least two first metal unit layers (411). One first metal unit layer (411) has a coplanar first low-frequency transmission channel (4111) and a first high-frequency deflection channel (4112), and the other first metal unit layer (411) has a coplanar first low-frequency deflection channel (4113) and a first high-frequency transmission channel (4114). The first low-frequency transmission channel (4111) corresponds to the first low-frequency deflection channel (4113), and the first high-frequency deflection channel (4112) corresponds to the first high-frequency transmission channel (4114).

2. The dual-band chromatic aberration-free beam scanning antenna according to claim 1, characterized in that: The dual-frequency feed (2) includes a first power divider network layer (21), a second power divider network layer (22), and an antenna radiation layer (23). The antenna radiation layer (23) contains a plurality of Ku radiation units (231) connected to the first power divider network layer (21) and a plurality of Ka radiation units (232) connected to the second power divider network layer (22).

3. The dual-band colorless beam scanning antenna according to claim 2, characterized in that: The multiple Ku radiating units (231) and Ka radiating units (232) are arranged in a nested configuration.

4. The dual-band colorless beam scanning antenna according to claim 1, characterized in that: The dual-channel dispersion compensation layer (42) includes at least one second metal unit layer (421), which is composed of multiple dual-channel subarrays (4211). The dual-channel subarrays (4211) have a coplanar second low-frequency transmission channel (42111) and a second high-frequency transmission channel (42112), and the transmission phases of the multiple dual-channel subarrays (4211) are distributed in an arithmetic sequence.

5. A dual-band colorless beam scanning antenna according to claim 4, characterized in that: Within the high-frequency bandwidth of the adjacent dual-channel subarray (4211), the slope of the transmission phase with respect to frequency is arranged in an arithmetic sequence, and within the low-frequency bandwidth of the adjacent dual-channel subarray (4211), the slope of the transmission phase with respect to frequency is arranged in an arithmetic sequence.

6. The dual-band chromatic aberration-free beam scanning antenna according to claim 1, characterized in that: The double-layer hollow rotating mechanism (3) includes an upper outer ring (31), a support ring (32), a lower outer ring (33), and two driving parts (34). The support ring (32) is mounted on the base (1) via a support member (17). The upper outer ring (31) and the lower outer ring (33) are respectively rotatably sleeved on both sides of the axis of the support ring (32). The two metasurface plates (4) are respectively disposed inside the upper outer ring (31) and the lower outer ring (33). The two driving parts (34) are disposed on the base (1) and drive the upper outer ring (31) and the lower outer ring (33) to rotate independently.

7. A dual-band chromatic aberration-free beam scanning antenna according to claim 6, characterized in that: The drive unit (34) includes a drive motor (341) and a drive gear (342), and gear rings that mesh with the drive gear (342) are formed on the outer side walls of the upper outer ring (31) and the lower outer ring (33).

8. An antenna array, characterized in that: The device includes multiple beam scanning antennas as described in claim 6 or 7, wherein the base (1) and the support ring (32) are set as polygons of the same shape, the multiple beam scanning antennas are spliced ​​together to form an antenna array, the multiple polygonal bases (1) are spliced ​​together, the multiple polygonal support rings (32) are spliced ​​together, one driving unit (34) drives the upper outer ring (31) of the multiple beam scanning antennas to rotate, and another driving unit (34) drives the lower outer ring (33) of the multiple beam scanning antennas to rotate.

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