Method and system for dynamic rf band allocation

Abstract

Methods and systems for band allocation are provided. A tunable / selectable bandpass filter based on time and location changes of a user equipment is disclosed. In addition, a method of allocating and optimizing an upload band and a download band to mitigate intermodulation distortion due to intermodulation distortion effects from a strong uplink channel is provided.

Description

[0001] Cross-references to related applications

[0002] This disclosure claims priority to U.S. Provisional Patent Application No. 63 / 068,782, filed August 21, 2020, the entire contents of which are incorporated herein by reference. Technical Field

[0003] This disclosure relates to RF (radio frequency) band allocation, and more particularly to methods and apparatus for dynamically allocating / selecting RF bands and subbands for use by RFFE (RF front-end) devices. Background Technology

[0004] RF spectrum is a shared resource used for communications. To avoid interference between services, the spectrum is divided into frequency bands and sub-bands, which are then allocated for the transmission and reception of RF signals. Allocation is both a political and regulatory issue (assigned to services by government entities or equivalent bodies) and a technical issue (assigned by base stations or user equipment to obtain optimal reception). Problems with RF allocation include the fact that political allocations can change over time and across different geographical regions, and that signal transmission on the selected transmission bands can generate nonlinear mixed intermodulation products and harmonics that can lead to intermodulation distortion and reduced receiver sensitivity. Summary of the Invention

[0005] The disclosed methods and apparatus address the described challenges and provide practical solutions to the aforementioned problems.

[0006] In a first aspect of this disclosure, a tunable filter is disclosed, configured to: select a passband on a first frequency band and a second frequency band, wherein the first frequency band overlaps with the second frequency band; determine the current time of the tunable filter; determine the location of the tunable filter; compare the current time with the frequency band availability time of a region; and, when the current time is equal to or after the frequency band availability time and the location is within the region, adjust the passband to cover frequencies available during the frequency band availability time of the region. The passband may be a 3dB passband.

[0007] In a second aspect of this disclosure, a tunable filter having a nominal passband with a selectable center frequency is disclosed. The tunable filter is configured to: determine the current time of the tunable filter; determine the location of the tunable filter; and select the center frequency of the nominal passband based on the current time, location, and a sequence of times based on region-specific frequency availability. The nominal passband may be a 3dB nominal passband.

[0008] In a third aspect of this disclosure, a selectable filter having multiple nominal passbands, each with a different center frequency, is disclosed. The selectable filter is configured to: determine the current time of a tunable filter; determine the location of the tunable filter; and select a nominal passband from the multiple nominal passbands based on the current time, location, and sequential time of frequency availability based on the region. The nominal passband may be a 3dB passband.

[0009] In a fourth aspect of this disclosure, a method is disclosed for reducing self-sensitivity degradation in a downlink passband caused by two or more uplink frequency bands transmitted in the uplink. The method includes: selecting two or more uplink frequency bands; selecting downlink frequency bands for an apparatus using the two or more uplink frequency bands; determining, by calculation, retrieval, or direct measurement, the intermodulation distortion values ​​of the available uplink frequency band combinations and the available downlink frequency bands; using the intermodulation distortion values ​​to determine whether intermodulation distortion exists for the downlink frequency bands given the two or more uplink frequency bands; determining, by link budget estimation, retrieval, or direct measurement, the link margin for each of the two or more uplink frequency bands; and increasing the modulation order of one or more uplink frequency bands having the largest link margin among the two or more uplink frequency bands. This method may be computer-implemented or implemented in hardware or firmware, or some combination thereof. Other aspects of this disclosure are provided in the specification, drawings, and claims of this application. The disclosure provided in the appendix A is incorporated herein by reference. Attached Figure Description

[0010] Figures 1A to 1C An example of passband allocation and adjustment is shown. Figure 1A A series of frequency bands and the passbands of filters covering a portion of these frequency bands are shown. Figure 1B This illustrates the adjustment of the passband based on the availability of new frequency allocations in the region (location). Figure 1C The passband is shown according to region and time.

[0011] Figure 2 A diagram of an example interfering party versus (vs.) the interfered party is shown, where the interfering party’s transmit channel (band / subband) causes intermodulation distortion (IMD) in the interfered party’s receive channel.

[0012] Figure 3 An example flowchart for avoiding or mitigating IMD receive channel allocation is shown.

[0013] Figure 4 An example flowchart is shown for avoiding or mitigating IMD receive channel allocation without power testing.

[0014] Figures 5A to 5CExample charts showing some sample modulation adjustments are provided.

[0015] Figures 6A to 6D An example graph illustrating the maximum sensitivity drop (MSD) for IMD is shown.

[0016] Figures 7A to 7D Example figures illustrating simulation results for modulation optimization used in IMD are shown.

[0017] Figures 8A to 8B An example system configuration for reducing sensitivity degradation is shown.

[0018] Figures 9A to 9E An example UE / base station configuration is shown.

[0019] Figure 10 An example of calculating the 7th order IMD is shown in a scenario with three interfering parties.

[0020] Figure 11 An example of an implementation of the method / system is shown. Detailed Implementation

[0021] Time and geographical allocation

[0022] User equipment (UE) used for radio frequency communication via base stations requires filters (e.g., bandpass, high-pass, low-pass) to avoid interference between frequency bands allocated by local authorities (e.g., governments) for a given communication service in the UE's region. For example, a cellular phone configured for U.S. network communications would have a passband configured for U.S. cellular phone communications within the United States.

[0023] Figure 1A Example configurations are shown of different frequency bands 110 allocated for different regions and services / operators, and example passbands 115 and 120 used by the UE. For this example, frequency bands B1 and B2 represent different service types for a first region (e.g., KDDI and SFBK for Japan), and frequency bands B3 through B6 represent different service types for a second region (e.g., bands n79, n77, n78, and C for the United States). Frequency band 110 can also be subdivided into sub-blocks or sub-bands 125. A first passband 115 is established for three frequency bands in the second region, and a second passband 120 is established for the remaining frequency bands in the second region. In some implementations, the passband is a 3dB passband. A 3dB passband corresponds to a frequency band where the gain or insertion loss remains within 3dB of the maximum gain or insertion loss.

[0024] Because the allocation of available sub-bands may change over time for different regions (e.g., governments expand frequency availability over time), some implementations include the ability to adjust the passband over time to accommodate newly allocated spectrum in the region. Figure 1B An example of adjusting the passband of a filter in a UE is illustrated. In a first time period, an initial passband 130 is established for a given area based on a first frequency allocation (e.g., an allocation prior to a transition date). In a second time period (e.g., after or at the transition date), the filter adjusts the passband 135 to accommodate the newly allocated spectrum. For example, in the United States, the initial passband may include a first portion of the C-band spectrum, namely the CB1 band between 3.7 GHz and 3.8 GHz expected to be licensed by the FCC at the start of the first time period, and the newly allocated spectrum may correspond to the CR2 band between 3.8 GHz and 3.98 GHz expected to be licensed by the FCC at or after the transition date at the start of the second time period. In some embodiments, the initial passband is approximately 3300 MHz to 3800 MHz before the extended band availability period (e.g., according to the regulatory authority), and the passband is adjusted to approximately 3300 MHz to 4000 MHz at or after the extended band availability period. As used herein and in the claims, "approximately" means within the range of 10%. In some embodiments, the filter may also shrink the passband to accommodate a reduction in spectrum allocation. In some implementations, adjustment 135 allows the filter range to avoid specific adjacent frequency bands 100 assigned to other services (e.g., the United States Integrated Fixed Satellite Service, FSS).

[0025] In this implementation, instead of adjusting the passband, the filter has multiple nominal passbands to choose from, and the center frequency of the passband is selected using region and time.

[0026] Figure 1C An example of a selectable / tunable filter for geographic and time purposes is shown. For example, a UE filter can be configured to select between: a conventional (e.g., before a given date) passband 140 for a second region, a new (e.g., after a given date) passband 150 for the second region, or a passband 155 for a first region. Thus, the passband is selected based on both time and location or region. In some implementations, this adjustment allows filter ranges 140, 150, 155 to avoid specific adjacent frequency bands 100 allocated to other services (e.g., satellites).

[0027] To determine passband adjustment / center frequency / selection based on time, the UE filter in the relevant implementation has the ability to determine the UE's time and / or date, which can then be compared with a programmed transition time / date (e.g., the date and time of a new spectrum allocation). This can be achieved via a local world clock on the UE, or by pushing the UE's time and / or date from the base station to the UE.

[0028] To determine passband adjustment / center frequency / selection based on location, the UE filter in the relevant implementation has the ability to determine the UE's location, which can then be compared with a programmed list of regions (e.g., the country / region where the UE is located). This can be achieved via the UE's local Global Positioning System (GPS), or by pushing the UE's location from the base station to the UE.

[0029] IMD avoidance

[0030] Another issue with frequency band allocation in the UE is intermodulation distortion (IMD) between the transmit and receive bands. When the UE is far from the base station, the transmission power on the uplink (UL) band (channel) may increase to maintain high fidelity at high bit rates. Transmission on multiple transmission channels with high average transmission power can lead to decreased sensitivity (i.e., self-desensitivity) in the UE receiver (downlink, DL) due to intermodulation products (e.g., harmonics) generated during uplink transmission within the downlink channel's frequency range.

[0031] Figure 2 An example diagram illustrates the IMD effects produced by the uplink (Tx) "aggressor" channel 205 and its corresponding sub-bands (SB1-a, SB1-b, SB1-c, SB1-d, SB2-a, etc.) in the downlink (Rx) "aggressor" bands 210 (Rx1, Rx2, Rx3, and Rx4) in intermodulation products from orders 2 to 7. Based on the IMD overlap in the Rx bands, some IMD effects 215 are more severe than others: generally, the lower the IMD order, the greater the potential distortion. As the order increases, the bandwidth of the resulting IMD increases, thus expanding the power of the IMD products over a larger bandwidth. For IMD products with the same total power but different orders, the power spectral density of the higher-order IMD will be less than that of the lower-order IMD. Uplink / downlink relationships can be categorized as "clean" and "interfering." In some implementations, a "clean" band 220 is a downlink band in which the corresponding uplink channel frequencies do not cause IMD products to fall into the Rx downlink band, while an "interference" relationship is a combination of uplink channel frequencies that cause IMD products 215 to fall into the Rx downlink band. In some implementations, a "clean" band only needs to be free of distortion in some lower IMDs. For example, a band with distortion only in 5th to 7th order IMDs can also be considered "clean" because the distortion in these IMDs can be considered insignificant for a given application.

[0032] Ideally, the UE selects uplink and downlink channels / subbands that provide only clean frequency bands, but this is not always an option for various reasons. Therefore, methods to mitigate IMD effects can be used. In some implementations, methods to mitigate IMD effects include increasing the modulation order of at least one of the uplink frequency bands. In some implementations, this is based on an estimate of the link budget for the uplink frequency band, thus focusing the increase in modulation order on the interfering party or the Tx uplink with the maximum link margin.

[0033] Figure 3 An example flowchart of an uplink / downlink allocation method with mitigated self-sensitivity degradation is shown. This example method is shown from the perspective of the UE, where the UE makes decisions and calculations; however, alternative implementations include a remote server (e.g., at a base station) performing some or all of the calculations and decisions, and then transmitting the data to the UE. The initial selection of the uplink UL band and downlink DL band is selected by standard means 305. IMD products are determined for all available uplink and downlink band combinations 310. These IMD products can be determined by the UE's real-time calculations or retrieved from a lookup table (LUT). The initial uplink and downlink bands are referenced against the determined IMD values ​​315 to see if there is any IMD overlap in the selected DL band. If there is no overlap (or if the DL band is "clean" relative to the IMD products generated by transmission over the selected UL band / subband), communication is performed using the initially selected UL band and DL band 320. If overlap exists, the average power level of the UL band is calculated and compared with a power threshold 330. If the average power is not higher than the threshold, communication is performed using the initially selected UL and DL bands 320. If the average power is higher than the threshold, further optimization is performed. For cases where the average power equals the threshold, the decision path is determined arbitrarily by the system being programmed.

[0034] In some implementations, the 325 threshold power is determined by a maximum sensitivity drop calculation, which is performed in real time or presented in a LUT. Figures 6A to 6D The fourth order ( ) is shown in the DL band CB2 from the UL bands B71 and B66. Figures 6A to 6B ) and 5th order ( Figures 6C to 6D Example diagram of MSD calculation.

[0035] The formula for IMD can usually be expressed as:

[0036] IMD n =c1*Aggr1+c2*Aggr2+c3*Aggr3+…c m *Aggr m (Equation 1); and

[0037]

[0038] Among them, IMD n It is the frequency bandwidth (i.e., frequency range) of the IMD order n. c i is the IMD coefficient (or IMD exponent) of the i-th interfering party (e.g., UL) frequency band, m is the number of interfering party frequency bands (can be more than two), and Agggr i It is the bandwidth frequency of the i-th interfering party. In some cases, the IMD index value can be negative.

[0039] Figure 10 An example of calculating the 7th-order IMD is shown in a three-interference scenario 1005 (three UL sub-bands: B14a at 788MHz to 793MHz, n5d at 839MHz to 844MHz, and B66e at 1750MHz to 1760MHz) and a interfered-side band 1010 (B48 at 3550MHz to 3500MHz). Two IMDs are calculated based on the general formula in Equation 1: the first 1015 is 1*Aggr1 + (-3)*Aggr2 + 3*Aggr3, and the second 1020 is (-2)*Aggr1 + (-3)*Aggr2 + 3*Aggr3. Note that for this example, n = |1| + |-3| + |3| = |-2| + |-3| + |3| = 7, which shows that these IMDs are the 7th-order IMDs according to Equation 2.

[0040] Figure 6A and Figure 6B The fourth-order IMD is shown to be 1*B66c+3*B71g. Figure 6C and Figure 6D The fifth-order IMD is shown to be 3*B66c+(-2)*B71g.

[0041] In some implementations, the power threshold is determined by UE calibration and test data.

[0042] In some implementations, if the average power level is above a threshold, the UE determines 335 whether there is an available "clean" frequency band for new UL and DL allocation 340, and continues with the corresponding UL frequency band / subband allocation as a first optimization. In some implementations, the UE does not check for available "clean" frequency bands but only performs secondary optimization 350. In some implementations, the UE may perform secondary optimization even if it checks and confirms the availability of a "clean" frequency band. In 3GPP-compliant implementations, allocation refers to the allocation of "resource blocks" (RBs) within a frequency band or subband, where a resource block is a frequency resource element allocated to a user, such as a user equipment (UE). In some implementations, frequency allocation is performed on a per-subcarrier basis. For example, in NB-IoT (narrowband "Internet of Things") applications, a single subcarrier may be used in the UL. In some implementations, an RB consists of 12 subcarriers. Secondary optimization 350 is performed if a clean frequency band cannot be found (or cannot be allocated for some reason). In some implementations, UE calibration data may be used to determine a power threshold 325 when Rx sensitivity degradation begins to occur. In other implementations, the power threshold can be determined using a predetermined data lookup table or by real-time monitoring of the interference IMD power level via the Rx channel. Another alternative is to calculate the expected level of sensitivity degradation using the desired transmit power level, the uplink transmission frequency, the downlink frequency used, and the nonlinear behavior of the cellular RF front-end circuitry. This calculation will follow known methods for determining the maximum allowable sensitivity degradation (MSD) under regulatory standards (e.g., 3GPP standards).

[0043] In the second optimization 350, this power threshold can be used to more accurately determine the impact of the modulation scheme / order on each UL band.

[0044] Secondary optimization 350 utilizes link budget estimation 345 on the selected UL bands (e.g., two or more UL bands for synchronous UL transmission) (and optionally, UE calibration data). If sufficient link budget margin exists in any UL, the UE increases the modulation order of the link with the largest link margin to the highest possible order supported by the link budget. In some implementations, if two uplinks have similar margins, the UE increases the modulation order of the UL with the higher IMD exponent / coefficient, as referred to herein. Figure 5C As described. In some implementations, if two uplinks have similar margins, the UE increases the modulation order of all ULs with sufficient margin.

[0045] Figure 4An alternative example flowchart for an uplink / downlink allocation method with mitigated self-sensitivity degradation is shown. Initial selection of the uplink UL band and downlink DL band is performed using standard means 405. IMD products are determined for all available uplink and downlink band combinations 410. These IMD products can be determined through real-time calculation at the UE or retrieved from a lookup table (LUT). The initial uplink and downlink bands are referenced to the determined IMD values ​​415 to check for any IMD overlap in the selected DL band. If no overlap exists (or if the DL band is "clean" for the selected UL band / subband), communication continues with the initially selected UL and DL bands 420. No power thresholds are determined or compared: the UE only checks 435 whether a clean band can be allocated and performs either a first optimization (clean band allocation) 440 or a second optimization 450 based on the result. The second optimization 450 is still based on a link budget estimate 445, but may not have available UE calibration data. This method can be used, for example, when it is determined that the UE is far from the base station, so high power Tx can be assumed.

[0046] Figures 5A to 5C Example parameters for different modulation schemes are shown in ascending order from QPSK to 256QAM. As shown in the table, the increasing modulation schemes reduce the average power in the UL band (typically 2dB to 4.5dB lower for the same UE power class rating), thereby mitigating the degradation of IMD self-sensitivity. Furthermore, throughput may increase (e.g., 4 bits for QPSK versus 16 bits for 16QAM).

[0047] Figure 5A The table shows the generalized third-order IMD (IMD3) behavior of coherent wave (CW) and the corresponding output power Pout value for QPSK normalization to 0 dBm. Figure 5A It was also shown that as the modulation order increases, the sensitivity of IMD3 and ACLR (adjacent channel leakage ratio) to changes in Pout decreases.

[0048] Figure 5B The figure shows simulation results for the maximum and actual sensitivity drops (MSD and ASD), respectively, for two uplinks (2UL) on 3GPP NR (New Radio) bands n71 and n66, and for DL ​​on the C-band 2 (CB2) band, which is dedicated to the United States and ranges from 3.8 GHz to 3.98 GHz. The ASD value decreases with increasing modulation order. Figure 5C This demonstrates the following fact: A higher IMD index (c) iIncreasing the modulation order of the frequency has the greatest impact on reducing sensitivity degradation, and therefore, when multiple ULs may have similar margins, it is preferable to use a larger c. i UL associated with the index.

[0049] exist Figure 5C In the equation, when (3x)n71 (i.e., IMD exponent of 3) moves from QPSK to 16QAM, a delta (Δ) decrease of 3.4 dB is obtained, while when (1x)n66 (i.e., IMD exponent of 1) moves from QPSK to 16QAM, a delta decrease of 1.42 dB is obtained. It should be noted that... Figure 5C In general, it is expected that the link budget on n71 (uplink of approximately 700MHz) is greater than that on n66 (uplink of approximately 1800MHz) because n71 is a relatively low frequency band (i.e., the link budget on n71 (uplink of approximately 700MHz) is expected to have more margin than that on n66 (uplink of approximately 1800MHz) because n71 is a relatively low frequency band with better propagation characteristics and therefore has a much larger range capacity). Figures 7A to 7D An example simulation result shows the deterioration of IMD sensitivity due to the increased modulation scheme. Figure 7A The input signal 705 and the corresponding unoptimized output are shown. As shown, the output indicates that the power level outside the signal is close to that of the signal (peaks around 5MHz to 15MHz, + and -), resulting in a significant degradation in sensitivity. Figures 7B to 7D The diagram shows that increasing the modulation order results in an increased reduction in the adjacent channel leakage ratio (ACLR) at each step. As the average power decreases, the signal becomes more distinct from the surrounding IMD, thus reducing self-sensitivity degradation. Similar to the effect of the 3rd order IMD, the ACLR follows a similar improvement in out-of-band interference as the average power decreases. Figures 7A to 7D As shown, a nonlinear device with third-order nonlinearity will improve its nonlinear behavior (lower impairment) by increasing the modulation order to cause lower input power.

[0050] Figure 8A and Figure 8B An example scenario is shown in which the IMD overlap and MSD reduction techniques described in this paper can be applied. Figure 8A An example is shown where a first interfering transmitter 815 and a second interfering transmitter 810 are simultaneously transmitted on separate antennas 820 (an alternative implementation of this system may transmit on a single antenna). Figure 8BAs shown, the intercepted receiver in the intercepted party's DL band can also have a reception path on a different module 805, or can be combined with one or more interfering transmitters 830. How the RF front end is configured can affect the UE's sensitivity to self-sensitivity degradation. For a given configuration, the UE can determine the expected level of sensitivity degradation for a given intercepted party's transmitted power level in a stored lookup table or through real-time calculation.

[0051] Figure 8B An example system is shown that generates transmit IMD products 835 (3rd order, low, and high in this example) throughout the circuit components 830 and 840 of the RF front end. When the IMD... n When the frequency is within the affected party's frequency band, IMD overlap will occur. For example... Figure 8B As shown, the tripod 845 is illustrated as having two Tx signals (Tx1 and Tx2) 825 reaching its input port 850 and output port 855. The tripod 845 has finite linearity and can be a source of IMD products. If any IMD... n With the frequency aligned with the bandwidth of the Rx target, IMD products will pass through the Rx receiving path unimpeded, and if this level is higher than the target sensitivity level, it can reduce the sensitivity of the Rx receiver.

[0052] Figures 9A to 9E Example base station and UE configurations are shown for scenarios where IMD overlaps and the MSD reduction techniques described herein can be applied. Figure 9A A base station 905 is shown with a computer control 910 communicating with a user equipment 915 (e.g., a mobile phone or tablet). The method can be performed on the UE 915 (selecting Tx and Rx channels for itself), on the computer 910 at the base station 905, or in some combination of both (e.g., the phone selects the channel, but the remote computer performs IMD calculations). In an implementation where the computer 910 performs one or more steps of the method, relevant information (e.g., channel allocation, IMD values, modulation selection, real-time measurements such as the current sensitivity degradation level, link budget margin, etc., on the UE's Rx receive path) can be sent from the base station 905 to the UE 915. Figure 9B A similar setup is shown, but in which the computer control 910 is also located away from the base station 905 (e.g., a central base station control system). The same option given for 9A also applies to 9B.

[0053] Figures 9C to 9E An example configuration including IAB (Integrated Access and Backhaul) is shown. Figure 9C An example of a UE communicating directly with a base station (UL and DL) is shown. Figure 9D An example of a UE that communicates only with the IAB is shown. Figure 9E An example of a UE communicating with both the base station and the UE is shown. Figures 9C to 9E The dashed lines in the text indicate that UL and DL may cause self-sensitivity degradation.

[0054] Figure 11 Example diagrams are shown illustrating implementations of desensitization mitigation in various uplink scenarios.

[0055] The circuits and devices according to the invention can be used alone or in combination with other components, circuits, and devices. Embodiments of the invention can be manufactured as integrated circuits (ICs), which can be packaged in IC packages and / or modules for ease of handling, manufacturing, and / or performance improvement. In particular, IC embodiments of the invention are typically used in modules, where one or more such ICs are combined with other circuit blocks (e.g., filters, amplifiers, passive components, and possible additional ICs) into a package. The ICs and / or modules are then typically combined with other components typically located on a printed circuit board to form end products such as cellular phones, laptops, or tablet computers, or to form advanced RF modules that can be used in various products such as vehicles, test equipment, and medical devices. Through various configurations of modules and components, such ICs are typically capable of implementing communication modes that are typically wireless communications.

[0056] Several embodiments of the present invention have been described. It should be understood that various modifications can be made without departing from the spirit and scope of the invention. For example, some of the steps described above may be independent of order and therefore may be performed in an order different from that described. Furthermore, some of the steps described above may be optional. The various actions described with respect to the above methods may be performed in a repetitive, serial, or parallel manner.

[0057] It should be understood that the foregoing description is intended to illustrate, rather than limit, the scope of the invention, which is defined by the scope of the appended claims, and other embodiments are within the scope of the claims. (Note that the bracketed markings of the claim elements are for ease of reference and do not in themselves indicate a particular order or enumeration of the elements; furthermore, such markings may be repeated in dependent claims as references to additional elements and are not considered as a sequence of markings that initiates conflict.)

Claims

1. A method for reducing self-sensitivity degradation in a downlink frequency band caused by two or more uplink frequency bands transmitted in the uplink, the method comprising: Select two or more uplink frequency bands; Select a downlink band for a device that uses the two or more uplink bands; The intermodulation distortion values ​​of the available uplink frequency band combinations and the available downlink frequency bands are determined by calculation, retrieval, or direct measurement. The intermodulation distortion value is used to determine whether intermodulation distortion exists for the downlink band, given the two or more uplink bands. as well as In response to determining the presence of intermodulation distortion for the downlink band, the average power of the two or more uplink bands is compared with a power threshold, and when the average power exceeds the power threshold, one of the following is performed: (a) Allocate the uplink transmission to a clean frequency band determined to be free of the intermodulation distortion; or (b) When a clean band is not available for allocation, determine the link margin of each of the two or more uplink bands to identify the uplink band with the largest link margin, and then increase the modulation order of the identified uplink band.

2. The method according to claim 1, wherein, The selection of the two or more uplink frequency bands is performed in at least one transmitter of the uplink transmission.

3. The method according to any one of claims 1 and 2, wherein, Determining the intermodulation distortion value is performed in at least one transmitter of the uplink transmission.

4. The method according to any one of claims 1 and 2, further comprising increasing the modulation order of one or more uplink frequency bands having the maximum link margin among the two or more uplink frequency bands, wherein, The increase in modulation order is performed in at least one transmitter of the uplink transmission.

5. The method according to claim 4, wherein, The at least one transmitter is included in the user equipment.

6. The method according to claim 1, wherein, The selection of the uplink frequency band is performed in the receiver of the uplink transmission.

7. The method according to any one of claims 1 and 6, wherein, The determination of intermodulation distortion is performed in the receiver of the uplink transmission.

8. The method according to any one of claims 1 and 6, further comprising increasing the modulation order of one or more uplink frequency bands having the maximum link margin among the two or more uplink frequency bands, wherein, The increase in modulation order is performed in the receiver of the uplink transmission.

9. The method according to claim 6, wherein, The receiver for the uplink transmission is included in one or more base stations, or one or more integrated access and backhaul (IAB) units, or both.

10. The method according to claim 1, wherein, The selection of the uplink frequency band is performed partly in the receiver of the uplink transmission and partly in the transmitter of the uplink transmission.

11. The method according to any one of claims 1 and 10, wherein, The determination of intermodulation distortion is performed partly in the receiver of the uplink transmission and partly in the transmitter of the uplink transmission.

12. The method according to any one of claims 1 and 10, further comprising increasing the modulation order of one or more uplink frequency bands having the maximum link margin, wherein, The increase in modulation order is performed partly in the receiver of the uplink transmission and partly in the transmitter of the uplink transmission.

13. The method according to any one of claims 1 and 2, wherein, The method is implemented on a user device.

14. The method according to claim 13, wherein, The user equipment is a mobile phone.

15. The method according to any one of claims 1 and 2, wherein, The method is implemented on a computer controlling a base station communicating with a user equipment, and the method further includes the base station sending instructions to the user equipment regarding channel allocation and modulation selection.

16. The method according to claim 15, wherein, The computer is located in the base station.

17. A method for reducing self-sensitivity degradation in a downlink band due to two or more uplink bands transmitted in the uplink, the method comprising: Select two or more uplink frequency bands; Select a downlink band for a device that uses the two or more uplink bands; The intermodulation distortion values ​​of the available uplink frequency band combinations and the available downlink frequency bands are determined by calculation, retrieval, or direct measurement. The intermodulation distortion value is used to determine whether intermodulation distortion exists for the downlink band, given the two or more uplink bands. The link margin of each of the two or more uplink frequency bands is determined by link budget estimation, retrieval, or direct measurement. Increase the modulation order of one or more uplink frequency bands with the largest link margin among the two or more uplink frequency bands; as well as If the link margin of the two or more uplink frequency bands is within the threshold difference, increase the modulation order of the uplink frequency band that does not have the maximum link margin among the two or more uplink frequency bands.

Images