Square circuit, control method of square circuit and control module

Abstract

The embodiment of the invention provides a self-adjustable squaring circuit, a control method of the squaring circuit and a control module, and the squaring circuit comprises a squaring unit which is used for outputting a first signal; the mirror image squaring unit is used for outputting a second signal; a temperature sensor; a storage module; the current adjusting module is used for receiving the target control signal and generating compensation current, the magnitude of the compensation current is related to the target control signal, and the output end of the current adjusting module is connected with the output end of the square unit or the mirror image square unit and used for compensating the difference between the first signal and the second signal; wherein the target control signal is obtained by the control module through table look-up in the storage module based on the current temperature. According to the embodiment of the invention, circuit mismatch can be improved, and the dynamic range is expanded.

Description

Technical Field

[0001] The present disclosure relates to the field of communication technology, and in particular to a square circuit, a control method for the square circuit, and a control module. Background Art

[0002] Detectors are usually used to measure the amplitude or power of a signal and are widely used in wireless systems. They can be simply divided into two categories: logarithmic amplifier detectors (or envelope detectors) and root mean square (RMS) detectors. For the root mean square detector, three operations need to be performed on the signal: root (Root), average (Mean), and square (Square). Among them, since the square unit has its own DC working current / voltage, this part of the current / voltage needs to be subtracted, so an additional mirror square unit is used to provide the same bias for accurate subtraction of the corresponding DC voltage / current. However, there may be a mismatch problem between the square unit and the mirror square unit, and the mismatch may change with temperature, resulting in the inability to accurately subtract the corresponding DC voltage / current, resulting in inaccurate output results. Summary of the invention

[0003] Embodiments of the present disclosure provide a squaring circuit, a control method for a squaring circuit, and a control module.

[0004] In a first aspect, an embodiment of the present disclosure provides a self-adjustable square circuit, comprising: A squaring unit, used to square the received AC signal, the squaring unit receiving a bias voltage and the AC signal, and an output end of the squaring unit outputting a first signal; A mirror square unit, used for receiving the bias voltage, wherein the structure of the mirror square unit is consistent with the structure of the square unit, and the output end of the mirror square unit outputs a second signal; Temperature sensor, used to detect the current temperature; a current adjustment module, configured to receive a target control signal and generate a compensation current, wherein the magnitude of the compensation current is related to the target control signal, wherein an output end of the current adjustment module is connected to an output end of the square unit or the mirror square unit, and is configured to compensate for a difference between the first signal and the second signal; wherein the target control signal is obtained by the control module by looking up a table in the storage module based on the current temperature; The storage module is used to store the corresponding relationship between the temperature and the target control signal.

[0005] In a second aspect, an embodiment of the present disclosure provides a control method for a squaring circuit, which is applied to the squaring circuit in the first aspect, and the method includes: Get the current temperature; A search is performed in the storage module according to the current temperature to obtain a target control signal, and the target control signal is output to the current adjustment module.

[0006] In a third aspect, an embodiment of the present disclosure provides a control module, including a processor and a memory; The processor is used to execute instructions stored in the memory so that the control module performs the control method as described in the second aspect.

[0007] The beneficial effects of the present disclosure are: If there is a process mismatch between the square unit and the mirror square unit, the first signal and the second signal output by the square unit and the mirror square unit are different, and the process mismatch changes with temperature. The temperature sensor is used to detect the current temperature of the square circuit; the storage module is used to store the corresponding relationship between the temperature and the target control signal. The control module can determine the target control signal for compensating the mismatch according to the current temperature; the current adjustment module receives the target control signal and generates a compensation current. The compensation current can compensate for the difference between the first signal and the second signal, eliminate (or at least partially eliminate) the inaccuracy caused by the mismatch between the square unit and the mirror square unit, and can compensate for the change of the mismatch with temperature.

[0008] Because the storage module stores the corresponding relationship between the temperature and the target control signal, when calibrating, it is only necessary to find the corresponding target control signal according to the temperature, without traversing all the control signals, thus saving calibration time. BRIEF DESCRIPTION OF THE DRAWINGS

[0009] Figure 1 A schematic diagram of input and output of signal envelope detection provided by an embodiment of the present disclosure; Figure 2 A schematic diagram of the architecture of an RMS detector provided in an embodiment of the present disclosure; Figure 3 A schematic diagram of a circuit structure of a square circuit provided in an embodiment of the present disclosure; Figure 4 A schematic diagram of an equivalent circuit of a square circuit provided in an embodiment of the present disclosure; Figure 5 A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 1 ; Figure 6 A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 2 ; Figure 7 A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 3 ; Figure 8A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 4 ; Fig. 9 A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 5 ; Fig.10 A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 6 ; Fig.11 The structure diagram of the current adjustment module provided in the embodiment of the present disclosure is as follows: Figure 1 ; Fig.12 The structure diagram of the current adjustment module provided in the embodiment of the present disclosure is as follows: Figure 2 ; Fig.13 The structure diagram of the current adjustment module provided in the embodiment of the present disclosure is as follows: Figure 3 ; Fig.14 A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 7 ; Fig.15 A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 8 ; Fig.16 A schematic diagram of the composition structure of a self-adjustable square circuit provided in an embodiment of the present disclosure Figure 9 ; Fig.17 A schematic diagram of a flow chart for obtaining a corresponding relationship and determining a target control signal provided in an embodiment of the present disclosure. DETAILED DESCRIPTION

[0010] The following will be combined with the drawings in the embodiments of the present disclosure to clearly and completely describe the technical solutions in the embodiments of the present disclosure. It is understood that the specific embodiments described herein are only used to explain the relevant disclosure, rather than to limit the disclosure. It should also be noted that, for the convenience of description, only the parts related to the relevant disclosure are shown in the drawings.

[0011] Unless otherwise defined, all technical and scientific terms used herein have the same meaning as those commonly understood by those skilled in the art to which the present disclosure belongs. The terms used herein are only for the purpose of describing the embodiments of the present disclosure and are not intended to limit the present disclosure.

[0012] In the following description, reference is made to “some embodiments”, which describe a subset of all possible embodiments, but it will be understood that “some embodiments” may be the same subset or different subsets of all possible embodiments and may be combined with each other without conflict.

[0013] It should be pointed out that the terms "first\second\third" involved in the embodiments of the present disclosure are merely used to distinguish similar objects and do not represent a specific ordering of the objects. It can be understood that "first\second\third" can be interchanged in a specific order or sequence where permitted, so that the embodiments of the present disclosure described here can be implemented in an order other than that illustrated or described here.

[0014] Detectors can be divided into envelope detectors and RMS detectors. Figure 1 Figure 2 shows the detection results of the envelope detector and the RMS detector for the same RF signal. Figure 1 As shown in the figure, the RF signal is a high-frequency sine wave whose amplitude / phase changes with time. The envelope detector will detect the envelope output of the input signal, which is usually its logarithmic value, that is, the output result 1 in the figure; the RMS detector will detect the root mean square value (or power value) of the input signal, that is, the output result 2 in the figure, and its output voltage does not change with the shape of the signal or the peak-to-average ratio, where the peak-to-average ratio refers to the peak-to-average power ratio (PAPR). Figure 1 As shown, for the signal value of the RF input signal, the amplitude of the high-frequency sinusoidal wave oscillation is not fixed, and the ratio of the power corresponding to the peak value to the power corresponding to the average value is the peak-to-average ratio.

[0015] For the RMS detector, its implementation is usually to perform three Root-Mean-Square operations on the signal, that is, the output voltage or current is: Formula (1) Where Y is the output voltage or current, X is the input voltage or current, and s is the slope.

[0016] Since the absolute value of the input signal may be small, usually in dBm units, for formula (1), the absolute value of the output signal Y is also small. For example, when the power of the input signal changes from -40dBm to -20dBm and s=1, the voltage corresponding to the output signal Y only changes from 2.24mV to 22.4mV. The absolute value and dynamic range are extremely small, which is not conducive to post-stage detection. Therefore, the RMS detector usually processes the result Y into a logarithmic value before outputting it: Formula (2) Where Z is the actual output current or voltage of the converted detector, k is the logarithmic slope, b is the logarithmic intercept, k' is the logarithmic slope after the combined square root operation, and b' is the logarithmic intercept after the combined linear slope s. The logarithm in the formula can also be other bases as long as there is a logarithmic relationship.

[0017] When the latter stage adds the function of converting to logarithm, the Root operation in RMS can be directly removed from the logarithm and become part of the slope, without the need to use hardware to implement it. The slope s in the previous text will be added to the logarithmic intercept here to form a new logarithmic intercept, which will no longer affect the slope of the output signal Z. The following descriptions are all based on this.

[0018] Since the RMS detector performs an averaging operation on the input signal, no matter how high the frequency of the input signal is, after averaging over a certain time window, the output signal will be close to DC and will only change slowly with the change of the mean value of the input signal.

[0019] Common RMS detector architectures include Figure 2 As shown in (a) or (b), it includes a square unit, a mirror square unit, an operation module, an average capacitor, a logarithmic converter and a driver. The structure of the square unit and the mirror square unit is exactly the same. The square unit receives a bias voltage DC Bias (used to drive the square unit to work) and an RF input signal RF IN The mixed signal formed, the mirror square unit receives the bias voltage DC Bias or the bias voltage DC Bias + feedback voltage (Feedback, FD), and the feedback voltage Feedback can be generated by the operation module or the driver. The output signals of the square unit and the mirror square unit are subtracted through the operation module, and then the average operation is realized through the average capacitor, and then the logarithmic conversion is realized through the logarithmic converter, and finally the driver is driven to enhance, and finally the detection result signal OUT is output, which is equivalent to Figure 1 The logarithmic RMS value (or power value) is output in . The location of the average capacitor can be as follows Figure 2 As shown in (a) in the figure, it can be placed at the output end of the operation module, or it can be placed at the output end of the operation module. Figure 2 As shown in (b) in the figure, it is placed at the output end of the square unit.

[0020] That is to say, Figure 2 In the RMS detector shown, the averaging capacitor is used to average the signal. Since the square unit has its own direct current (DC) working current / voltage, this part of the current / voltage needs to be subtracted, so an additional square unit (i.e., mirror square unit) is used to provide the same bias for accurate subtraction of the corresponding DC voltage / current. Its input can also be a feedback voltage for square root operation. The average position can be adjusted as needed.

[0021] In an RMS detector, squaring and averaging operations are usually implemented together. Figure 3This is an example of a method for implementing a square unit. The dashed box contains two identical square units. Square unit 1 includes bipolar junction transistors (BJT, or triode) Q11~Q14, which are used to receive RF input. Square unit 2 is a mirror square unit, including BJT Q15~Q18, which is used to receive a reference voltage (or the same bias voltage as the RF branch). Its main function is to subtract the DC output voltage of the square unit, and sometimes it can also realize the square root function.

[0022] The two square units need a certain static DC current to work properly. Ideally, when there is no RF input, if the bias voltage of the two square units is the same, their DC bias current will also be the same, that is, the output current I11 of square unit 1 and the output current I12 of square unit 2 are the same. The same voltage is generated on the same resistors R11 and R12 ( Figure 3 Node 1 and node 2 in the figure are subtracted to produce a zero output. When an RF signal is input, an additional square current will be generated in the branch where the current I11 is located, which will be averaged by capacitors C11 and C12, and an additional square average voltage will be generated based on the DC voltage on resistor R11. Since the DC currents are exactly the same and are completely subtracted, the differential voltage output by the two square units is the precise square voltage.

[0023] However, in actual circuit manufacturing, even if the bias and design dimensions of the two square units are exactly the same, due to the mismatch of BJT or load resistors R11 and R12, the DC currents of the two square units are not completely equal, and the DC voltages at the two differential ends cannot be accurately subtracted. If the remaining term is set to the mismatch voltage Vos, equation (2) can be written as the following equation (3): Formula (3) Vos will enter the logarithm, add to the square average term, and cannot be taken out of the logarithm. When the input power is small, its square average term is also small, and may even be smaller than Vos, then the useful signal The mismatch voltage Vos will be covered and cannot be detected. If the mismatch voltage / current is high, it will significantly affect the lower limit of the input dynamic range, resulting in a loss of dynamic range.

[0024] The mismatch voltage / current is also at DC, and the square unit mismatch current achieved by devices such as BJT / Heterojunction Bipolar Transistor (HBT) may vary with temperature.

[0025] Due to the principle limitation of the square unit, the dynamic range of its output signal is strongly correlated with the dynamic range of the input signal. If you need to detect an input signal in the range of 60dBm, the output voltage / current will also change by 120dB, that is, 1 million times. If the upper limit of the output dynamic range is set to 1V, its lower limit will reach 1μV. If the mismatch is not additionally processed, it may reach several mV, which is much larger than the lower limit of the output voltage. If you want to increase the lower limit voltage higher than the square unit mismatch during design, such as increasing it to 10mV, the upper limit will increase to 10000V accordingly, which is obviously impossible to achieve.

[0026] The mismatch voltage Vos or mismatch current Ios is located in DC, and the useful signal It is also at DC or very low frequency, so the mismatch voltage / current cannot be suppressed by traditional DC offset elimination circuit (DCOC) feedback, capacitor isolation and other methods, because these methods will also suppress the useful signal inhibition.

[0027] Currently, the following techniques exist to deal with the square cell mismatch problem: The front RF analog variable gain amplifier (VGA) feeds the output of the square unit back to the control end of the VGA, converts the logarithm through the VGA, and compresses the input power range of the square unit, thereby reducing the demand for the dynamic range of the square unit. This solution does not reduce the mismatch, but only adjusts the input range of the square unit to the linear range of the square unit. However, due to the need to use RF VGA, the power consumption is extremely high, and the overall linear range of the system will be limited by the RF VGA.

[0028] The chopper chops the mismatch voltage or current to high frequency through the switches before and after the square unit, and filters out the mismatch at high frequency when averaging in the later stage, thereby achieving automatic mismatch suppression. However, since the chopper usually uses a metal-oxide-semiconductor field-effect transistor (MOSFET, MOS) or BJT switch, the parasitic capacitance of the switch may cause input RF leakage and affect input matching on the one hand, and may cause the driving clock of the chopper switch to feed through to the RF path on the other hand, forming a background noise, which in turn limits the dynamic range of the square unit. In addition, the driving clock of the chopper also requires additional power consumption.

[0029] For ease of understanding, the square circuit is abstracted as Figure 4 ,like Figure 4 As shown, Figure 4The input impedance of the device in the bold solid frame in (a) is equivalent to Figure 4 The resistor RL1 and the resistor RL2 + capacitor CM are shown in (b). The two square units have the same bias Bias, where the first end of the resistor RL1, the first end of the resistor RL2, and the first end of the capacitor CM are all connected to the power supply; the second end of the resistor RL1 and the second end of the capacitor CM are all connected to the output end of the square unit; the second end of the resistor RL2 is connected to the output end of the mirror square unit. The square unit inputs the RF signal RF IN , the mirror square unit inputs an optional feedback signal FB (for square root operation). Both have the same load, abstracted as resistors RL1 and RL2, and input RF signal RF IN The square unit also has a capacitive load CM for filtering, that is, taking the average value. Due to resistors RL1 and RL2, the current output of the two square units is converted into a voltage VOUT output. When there is no RF signal input, VOUT = 0 in the ideal case. However, due to manufacturing errors, VOUT may not be zero, that is, there is a mismatch.

[0030] Based on this, the embodiment of the present disclosure provides a self-adjustable square circuit, which uses a temperature sensor, a storage module and a current adjustment module to compensate for the process mismatch between the square unit and the mirror square unit. Among them, the temperature sensor is used to detect the current temperature of the square circuit; the storage module is used to store the correspondence between the temperature and the target control signal. The control module can determine the target control signal for compensating the mismatch according to the current temperature; the current adjustment module receives the target control signal and generates a compensation current. The compensation current can compensate for the difference between the first signal and the second signal caused by the process mismatch, eliminate (or at least partially eliminate) the inaccuracy caused by the mismatch between the square unit and the mirror square unit, and can compensate for the change of the mismatch with temperature.

[0031] The embodiments of the present disclosure will be described in detail below with reference to the accompanying drawings.

[0032] In one embodiment of the present disclosure, Figure 5 (or Figure 6 or Figure 7 ), the self-adjustable squaring circuit 10 (hereinafter referred to as the squaring circuit 10 ) includes a squaring unit 101, a mirror squaring unit 102, a current adjustment module 103, a control module 105 (or controller), a storage module 106, and a temperature sensor 107.

[0033] The square unit 101 is used to square the received AC signal. The square unit 101 receives a bias voltage and an AC signal. The output end of the square unit 101 outputs a first signal. A mirror image square unit 102 is used to receive a bias voltage. The structure of the mirror image square unit 102 is consistent with that of the square unit 101. The output end of the mirror image square unit 102 outputs a second signal. A temperature sensor 107, used to detect the current temperature of the square circuit 10; The storage module 106 is used to store the corresponding relationship between the temperature and the target control signal, and the target control signal is used to control the magnitude of the compensation current; The control module 105 is connected to the temperature sensor 107 and the output end of the storage module 106, obtains the current temperature, and performs a table lookup in the storage module 106 based on the current temperature to obtain a target control signal, wherein the target control signal is used to control the degree of current compensation for the output of the square unit 101 and / or the mirror square unit 102; The current adjustment module 103 is used to receive the target control signal and generate a compensation current. The size of the compensation current is related to the target control signal. The output end of the current adjustment module 103 is connected to the output end of the square unit 101 or the mirror square unit 102 to compensate for the difference between the first signal and the second signal.

[0034] It should be noted that if Figure 5 As shown, the signal at the output end of the square unit 101 is recorded as the first signal, and the signal at the output end of the mirror square unit 102 is recorded as the second signal. The square unit 101 and the mirror square unit 102 usually output current signals, which are converted into voltage signals through equivalent input impedance here, and the first signal minus the second signal is the output signal. In the description of the embodiments of the present disclosure, only the first signal and the second signal are used to represent the output end signals of the square unit 101 and the mirror square unit 102, and the voltage value and current value corresponding to the first signal and the second signal will be involved later.

[0035] The mirror square unit 102 can also receive a feedback signal ( Figures 5 to 7 not shown).

[0036] It should also be noted that the square unit 101 and the mirror square unit 102 can have the same circuit structure (refer to the aforementioned Figure 3 , but not limited to the above Figure 3), in the case of no RF input (i.e. no AC signal input), if there is no mismatch, the voltages corresponding to the first signal and the second signal have exactly the same voltage value (at this time, the voltage value of the output signal is 0). Due to the existence of mismatch, there will be a voltage difference between the voltages corresponding to the first signal and the second signal (i.e., the voltage value of the output signal), and the process mismatch changes with temperature. Specifically, at different temperatures, there is a difference in the voltage difference between the voltages corresponding to the first signal and the second signal. The storage module 106 pre-stores the corresponding relationship between the temperature and the target control signal, and the temperature sensor 107 is used to detect the current temperature of the square circuit 10; the control module 105 can determine the target control signal for compensating the mismatch according to the current temperature; the current adjustment module 103 receives the target control signal and generates a compensation current. The compensation current can compensate for the difference between the first signal and the second signal, eliminate (or at least partially eliminate) the inaccuracy caused by the mismatch between the square unit 101 and the mirror square unit 102, and the compensation current can change with the current temperature, thereby compensating for the change of the process mismatch with temperature.

[0037] Because the storage module 106 stores the corresponding relationship between the temperature and the target control signal, during calibration, it is only necessary to obtain the current temperature and search for the corresponding target control signal according to the current temperature (which can be understood as a table lookup), which can save calibration time. In other examples, the storage module 106 can also be independent of the square circuit 10, or integrated inside the control module 105, which is not specifically limited. Among them, the storage module 106 can be implemented in a variety of ways, such as a one-time programmable memory EFUSE, an on-chip read-only memory (ROM), an off-chip ROM connected via a serial peripheral interface (SPI) or other protocols, a display look-up table (LUT), etc.

[0038] In the disclosed embodiment, the square circuit 10 also includes a voltage acquisition module 104 for obtaining the corresponding relationship between the temperature and the target control signal. The voltage acquisition module 104 is connected to the output terminals of the square unit 101 and the mirror square unit 102, respectively, and is used to collect the output terminal voltage of the square unit 101 and the output terminal voltage of the mirror square unit 102. The voltage difference between the output terminals of the square unit 101 and the mirror square unit 102 when there is no AC signal input can be detected in advance at multiple different temperatures, and then multiple initial control signals are used to control the current adjustment module 103 to compensate for the mismatch, and the initial control signal that minimizes the voltage difference is selected as the target control signal. The preset multiple temperatures and the corresponding target control signals are all saved. When current compensation is performed, it is only necessary to look up the table according to the current temperature to obtain the target control signal that can minimize the mismatch, thereby realizing current compensation.

[0039] It should be noted that in the embodiment of the present disclosure, the voltage acquisition module 104 and / or the control module 105 can be a part of the square circuit 10, or can be an off-chip device independent of the square circuit 10, and there is no specific limitation on this. In the accompanying drawings, the voltage acquisition module 104 and the control module 105 are included in the square circuit 10 as an example.

[0040] It should also be noted that in the embodiments of the present disclosure, temperature may refer to the temperature of the circuit or the ambient temperature. The ambient temperature is usually relatively stable, and therefore generally refers to the temperature of the circuit itself.

[0041] It should also be noted that if Figure 5 As shown, the output end of the current adjustment module 103 is connected to the output end of the mirror square unit 102, that is, only the second signal is current compensated; or Figure 6 As shown, the output end of the current adjustment module 103 is connected to the output end of the square unit 101, that is, only the first signal is current compensated; or Figure 7 As shown, the current adjustment module 103 includes two output terminals, which are respectively connected to the output terminals of the square unit 101 and the mirror square unit 102, and the corresponding compensation current includes a first compensation current and a second compensation current, and current compensation is performed on the first signal and the second signal at the same time. Finally, when there is no AC signal input, the voltage values ​​corresponding to the first signal and the second signal are basically the same (a certain error range is allowed).

[0042] In the following, each component module and working process of the square circuit 10 is described in more detail in combination with the specific circuit structure.

[0043] In some embodiments, Figure 8 As shown, the current adjustment module 103 includes: The digital-to-analog converter 1031 is used to receive the control signal, perform digital-to-analog conversion on the control signal, and obtain a current control signal; wherein the control signal may be a digital signal, and the current control signal may be an analog signal, for example, the current control signal is a voltage analog signal; the control signal and the current control signal have a corresponding relationship, and when the control signal is different, the current control signal is different; The first current source I1 is used to receive a current control signal and generate a compensation current based on the current control signal, wherein the compensation current and the current control signal have a corresponding relationship, and when the current control signal is different, the compensation current is different.

[0044] It should be noted that the control signal is a target control signal or an initial control signal used when determining the target control signal. Figures 5 to 7 ) are referred to as control signals for explanation.

[0045] It should also be noted that in the embodiments of the present disclosure, the digital-to-analog converter is sometimes referred to as DAC (Digital to Analog Converter). Figure 8 As shown, taking the current compensation for the output of the mirror square unit 102 as an example, the output end of the first current source I1 is connected to the output end of the mirror square unit 102 to provide the compensation current to the output end of the mirror square unit 102, thereby realizing the current compensation for the second signal; or, if the output of the square unit 101 is current compensated, the output end of the first current source I1 is connected to the output end of the square unit 101 to provide the compensation current to the output end of the square unit 101, thereby realizing the current compensation for the first signal.

[0046] Further, such as Fig. 9 As shown, in some embodiments, the square circuit 10 may further include a third current source I3; the output end of the current adjustment module 103 is connected to the output end of the mirror square unit 102, and the output end of the third current source I3 is connected to the output end of the square unit 101; The third current source I3 is used to provide a fixed current to provide a fixed current to the output terminal of the square unit 101 .

[0047] It should be noted that, in other examples, the first current source I1 may be connected to the output end of the square unit 101 , and the third current source I3 may be connected to the output end of the mirror square unit 102 .

[0048] It should also be noted that the third current source I3 is an optional fixed current source, which provides a fixed current (that is, the current value is fixed) and is not controlled by the control signal output by the control module 105. The magnitude of the fixed current can be the magnitude of the current of the first current source I1 when the default control signal (that is, the control signal is an uncalibrated default value), that is, the fixed current of the third current source I3 provides a reference, so that the compensation current can be increased or decreased based on it, thereby realizing the "bidirectional" adjustment capability. For example, when there is no deviation between the currents output by the squaring unit 101 and the mirror squaring unit 102, the first current source I1 is in the default control signal, and the currents output by the first current source I1 and the third current source I3 are equal; when the current output by the squaring unit 101 is greater than the current output by the mirror squaring unit 102, the compensation current output by the first current source I1 can be increased through the control signal; when the current output by the squaring unit 101 is less than the current output by the mirror squaring unit 102, the compensation current output by the first current source I1 can be reduced through the control signal; therefore, compared with the compensation current under the default control signal, the control signal can control the increase or decrease of the compensation current to achieve bidirectional compensation.

[0049] In some embodiments, Fig.10 As shown, taking the square circuit 10 including two current adjustment modules 103 as an example, the two current adjustment modules 103 are respectively a current adjustment module 103-1 connected to the output end of the square unit 101 and a current adjustment module 103-2 connected to the output end of the mirror square unit 102. Correspondingly, the corresponding relationships stored in the storage module 106 include two: a corresponding relationship between temperature and a first control signal, and a corresponding relationship between temperature and a second control signal. The control signal output by the control module 105 based on the current temperature includes a first control signal and a second control signal. The current adjustment module 103-1 receives the first control signal, and based on the control of the first control signal, generates a first compensation current to compensate the output of the square unit 101 for current, and the current adjustment module 103-2 receives the second control signal, and based on the control of the second control signal, generates a second compensation current to compensate the output of the mirror square unit 102 for current.

[0050] Here, the current adjustment module 103-1 and the current adjustment module 103-2 may both include a digital-to-analog converter 1031 and a first current source I1. If there is a mismatch, the compensation currents generated by the two current sources are different in magnitude, that is, the compensation degrees of the two are different, thereby improving the mismatch.

[0051] It should also be noted that the compensation current has different targets and directions depending on the location where the first current source I1 is connected. Fig.10The mismatch of the circuit is: when there is no AC signal input, the voltage value corresponding to the first signal is greater than the voltage value corresponding to the second signal, then the voltage division of the resistor RL1 is less than the voltage division of the resistor RL2, and the current flowing through the resistor RL1 is less than the current flowing through the resistor RL2. Therefore, the compensation method can be: adjusting the first current source I1 connected to the mirror square unit 102, reducing the size of the second compensation current, so as to reduce the voltage division of the resistor RL2, thereby increasing the voltage value of the second signal; or adjusting the first current source I1 connected to the square unit 101, increasing the size of the first compensation current, so as to increase the voltage division of the resistor RL1, thereby reducing the voltage value of the first signal; the ultimate goal is to make the voltage value corresponding to the first signal and the voltage value corresponding to the second signal tend to be consistent, thereby achieving compensation.

[0052] In some embodiments, Fig.11 As shown, the first current source I1 includes an operational amplifier P1, a transistor Q1 and a resistor R1; wherein the non-inverting input terminal (+) of the operational amplifier P1 is connected to the output terminal of the digital-to-analog converter 1031 to receive a current control signal, the output terminal of the operational amplifier P1 is connected to the base of the transistor Q1, the emitter of the transistor Q1, the inverting input terminal (-) of the operational amplifier P1, and the first terminal of the resistor R1 are connected, the second terminal of the resistor R1 is grounded, and the collector of the transistor Q1 outputs a control current. Here, the transistor Q1 can be specifically a BJT or an NMOS tube, which is not specifically limited.

[0053] It should be noted that the control signal can be a multi-bit digital signal. Fig.11 The structure shown can convert the analog voltage (ie, the current control signal) output by the digital-to-analog converter 1031 into a compensation current, and the current value of the compensation current is the ratio of the voltage value of the current control signal to the resistance value of the resistor R1.

[0054] In some embodiments, Fig.12 As shown, the current adjustment module 103 includes: A voltage providing unit 1032 is used to provide a first voltage V1, and the voltage value of the first voltage V1 may be a fixed value; The resistance adjustment unit 1033 is connected to the first voltage V1 and receives a control signal, changes the resistance value based on the control signal, and outputs a compensation current, where the compensation current changes with the control signal.

[0055] It should be noted that if Fig.12As shown, the voltage providing unit 1032 may include an operational amplifier P2 and a transistor Q2, and the resistance adjusting unit 1033 includes a plurality of resistors connected in series, the plurality of resistors form a resistor string, and a switch transistor M1 is connected in parallel at both ends of the remaining resistors except the resistor R1, the plurality of switch transistors M1 are connected in series, the control signal is a multi-bit digital signal, and the control end of each switch transistor M1 receives a one-bit control signal. Among them, the transistor Q2 may be a BJT, and the switch transistor M1 may be a MOS tube. The positive input terminal (+) of the operational amplifier P2 receives a fixed voltage VB, and the fixed voltage VB does not change with temperature and power supply; the output terminal of the operational amplifier P2 is connected to the base of the transistor Q2; the emitter of the transistor Q2 is connected to the first end of the resistor string, and is connected to the inverting input terminal (-) of the operational amplifier P2, and the voltage at the connection node is the first voltage V1; the second end of the resistor string is grounded.

[0056] exist Fig.12 In the resistor R2 <1> ~R2 <4> The two ends of these four resistors are connected in parallel with the switching transistor M1 <1> ~M1 <4> For example, when the parallel switch transistor M1 is turned on, the corresponding resistor R2 is not connected to the resistor string for voltage division, so that the conduction of each switch transistor M1 is controlled based on the control signal, so as to change the resistance value of the resistor string, adjust the voltage division, and finally adjust the compensation current of the collector output end of the transistor Q2. It can be understood that compared with Fig.11 ,exist Fig.12 In this case, the D / A converter is combined with the circuit generating the compensation current, and there is no independent D / A converter. The compensation current = VB / (R1+resistance not short-circuited by the switch transistor). The BJT can also be replaced by an NMOS tube, and each switch transistor can be Fig.12 The shown one is an NMOS tube, but it can also be a CMOS transmission gate, etc., and the control signal is set accordingly.

[0057] For the third current source I3 (fixed current source), Fig.11 The digital-to-analog converter 1031 in the embodiment is removed, and a fixed control signal is directly inputted, and the value of the control signal is fixed, so that it outputs a fixed current; or Fig.12 By removing the switch transistor M1 in the circuit and directly designing a fixed resistor R1, a fixed current can be achieved.

[0058] It should also be noted that the resistance adjustment unit 1033 can also be multiple resistors connected in parallel, and a switching transistor is connected in series between some or all of the resistors and the first voltage V1 to achieve controllable resistance. Alternatively, the resistance adjustment unit can also be a voltage-controlled MOS, which controls the resistance based on voltage, and there is no specific limitation on this.

[0059] here, Fig.11 and Fig.12The circuits shown can all achieve current extraction, that is, the direction of the compensation current flows from the collector of the transistor Q1 / Q2 to the ground, and the collector of the transistor Q1 / Q2 is connected to the output end of the mirror square unit 102, so it is equivalent to current extraction. In the disclosed embodiment, the collector of the transistor Q1 / Q2 can also be connected to the input end of the PMOS current mirror, and the output end of the PMOS current mirror is connected to the output end of the mirror square unit 102. After the current mirror of the PMOS current mirror, the output current flows out of the PMOS current mirror, which is equivalent to current injection. For current injection, such as Fig.13 As shown, in some embodiments, the current adjustment module 103 includes: A second current source I2 receives a second voltage and generates a first current, wherein the second voltage may be a fixed voltage and the first current may be a fixed current; The current control circuit 1034 receives the first current and outputs a compensation current. The current control circuit 1034 adjusts the magnitude of the compensation current based on the control signal.

[0060] It should be noted that if Fig.13 As shown, the second current source I2 may include an operational amplifier P3 and a transistor Q3, and may also include a resistor R3; the current control circuit 1034 includes a current mirror structure and a plurality of transistors, the current mirror structure includes an input transistor M21 and an output transistor M22, the input transistor M21 receives the first current, and the output transistor M22 is used to proportionally replicate the first current to output a compensation current; a plurality of transistors M23~M2n, the control ends of the transistors M23~M2n are respectively connected to a switch, the control ends of the switches are used to receive control signals, the control signals can control the control ends of the transistors M23~M2n to connect to the power supply VDD or to the control end of the transistor M22, thereby realizing the conduction or disconnection of the transistors M23~M2n, so as to adjust the equivalent size of the output transistor M22 and adjust the size of the compensation current, and n is a positive integer greater than 2.

[0061] The non-inverting input terminal (+) of the operational amplifier P3 receives the second voltage, the output terminal of the operational amplifier P3 is connected to the base of the transistor Q3, and the emitter of the transistor Q3 is connected to the inverting input terminal (-) of the operational amplifier P3; the emitter of the transistor Q3 is grounded through the resistor R3; the collector of the transistor Q3 is connected to the first terminal (e.g., drain) and the control terminal (gate) of the transistor M21, and is connected to the control terminal of the transistor M22, and outputs the first current; the second terminals (e.g., sources) of the transistors M21~M2n are all connected to the power supply VDD; the first terminals of the transistors M22~M2n are all connected together for outputting the compensation current.

[0062] The control signal is a multi-bit signal, each bit corresponds to one of the transistors M23 to M2n, and is used to control the control end of the corresponding transistor to selectively connect to the power supply VDD or the control end of the transistor M21 ( Fig.13 The control signal is not shown in the figure). For example, when the control signal of the corresponding bit is a high-level logic 1, it is connected to the power supply VDD, and when the control signal of the corresponding bit is a low-level logic 0, it is connected to the control end of the transistor M21; or vice versa, which is not specifically limited. Among them, the transistors M21~M2n can all be PMOS tubes, whose control end is the gate, one of the first end and the second end is the source, and the other is the drain; the transistor Q3 can be a BJT.

[0063] In this way, the connection positions of the control terminals of the transistors M23 - M2n are controlled by the control signal, thereby controlling the magnitude of the output compensation current, thereby improving the mismatch of the square circuit 10 .

[0064] For the voltage acquisition module 104: In some embodiments, Fig.14 As shown, the voltage acquisition module 104 includes a first analog-to-digital converter 1041 and a switch unit SW; One end of the switch unit SW is connected to the first analog-to-digital converter 1041, and the other end is selectively connected to the output end of the square unit 101 or the output end of the mirror square unit 102; The first analog-to-digital converter 1041 is used to perform analog-to-digital conversion on the voltage at the output end of the square unit 101 or the mirror square unit 102 , and output the converted digital signal to the control module 105 .

[0065] It should be noted that if Fig.14 As shown, the voltage acquisition module 104 can acquire the voltage values ​​corresponding to the first signal and the second signal through an analog to digital converter (ADC), that is, the first analog to digital converter 1041, also recorded as ADC1. Specifically, the switch unit SW can be a single-pole double-throw switch, which includes three ports: A, B, and C. Among them, port A is connected to the output end of the square unit 101, port B is connected to the output end of the mirror square unit 102, and port C is connected to the input end of the first analog to digital converter 1041.

[0066] The control module 105 can also control the connection state of the switch unit SW. When the voltage difference does not need to be collected, the port C is not connected to either the port A or the port B. When the voltage difference needs to be collected, the control module 105 controls the port C to be connected to one of the ports A and B. For example, when obtaining the corresponding relationship between the temperature and the target control signal, the control module 105 first controls the port C to be connected to the port A, so that the first analog-to-digital converter 1041 collects the analog voltage of the first signal, converts it into a digital signal and sends it to the control module 105. Then the control module 105 controls the port C to be connected to the port B, so that the first analog-to-digital converter 1041 collects the analog voltage of the second signal, converts it into a digital signal and sends it to the control module 105. The control module 105 calculates the difference between the two received voltage values ​​to obtain the voltage difference. The voltage difference is used to determine whether there is a difference between the first signal and the second signal.

[0067] In some embodiments, Fig.15 As shown, the voltage acquisition module 104 includes a second analog-to-digital converter 1042 and a third analog-to-digital converter 1043; The second analog-to-digital converter 1042 is connected to the output end of the square unit 101, performs analog-to-digital conversion on the voltage at the output end of the square unit 101, and outputs the analog-to-digital conversion to the control module 105; The third analog-to-digital converter 1043 is connected to the output end of the mirror square unit 102 , performs analog-to-digital conversion on the voltage at the output end of the mirror square unit 102 , and outputs the converted voltage to the control module 105 .

[0068] It should be noted that the embodiment of the present disclosure may also not set the switch unit SW, but use two analog-to-digital converters to respectively collect the voltage values ​​corresponding to the first signal and the second signal. For example, when obtaining the corresponding relationship between the temperature and the target control signal, Fig.15 As shown, the second analog-to-digital converter 1042 (also denoted as ADC2) collects the voltage value of the first signal and sends it to the control module 105, and the third analog-to-digital converter 1043 (also denoted as ADC3) collects the voltage value of the second signal and sends it to the control module 105. The control module 105 calculates the difference between the two received voltage values ​​to obtain the voltage difference.

[0069] In combination with the above-mentioned figures and related descriptions, it can be seen that in the embodiment provided by the present disclosure, when obtaining the corresponding relationship between the temperature and the target control signal, the control module 105 is used to output the initial control signal to the current adjustment module 103, and the current adjustment module 103 performs current compensation on the first signal and / or the second signal based on the initial control signal. The voltage acquisition module 104 is used to collect the voltage values ​​corresponding to the first signal and the second signal, and send them to the control module 105, and the control module 105 determines the voltage difference between the first signal and the second signal to determine whether the first signal and / or the second signal can be appropriately compensated under the initial control signal. If the voltage difference between the first signal and the second signal is the smallest, zero or substantially zero, it means that the first signal and / or the second signal can be appropriately compensated under the initial control signal, and the initial control signal is confirmed as the target control signal; if the voltage difference between the first signal and the second signal is not the smallest, zero or substantially zero, it means that the first signal and / or the second signal cannot be appropriately compensated under the initial control signal.

[0070] In the embodiment of the present disclosure, when the current adjustment module 103 outputs the compensation current based on the target control signal, the difference between the first signal and the second signal is minimal, zero or substantially zero.

[0071] It should be noted that the difference between the first signal and the second signal here represents the difference between the corresponding current or voltage. As mentioned above, the ideal situation is that when there is no AC signal input, the first signal and the second signal are exactly the same and there is no difference. Here, when there is no AC signal input, the current adjustment module 103 performs circuit compensation on the first signal and / or the second signal based on the target control signal input compensation current, so that the difference between the first signal and the second signal is minimized (i.e., the lowest difference that can be achieved), zero (ideally, the difference is completely eliminated), or basically zero (in practice, it is difficult to completely eliminate the difference, and basically zero can be considered to meet a certain error range, for example, the voltage difference between the first signal and the second signal is less than a threshold, for example, less than 1%~5% of the swing of the AC signal, or the absolute value of the voltage difference between the first signal and the second signal is less than 1mV~10mV. This requirement is met and the voltage difference / current difference can be ignored).

[0072] In some embodiments, Fig.14 or Fig.15 As shown, the square circuit 10 may further include: The trigger module 108 is used to receive a reset signal and / or an external sampling signal, and when any one of the reset signal and the external sampling signal is in an enabled state, output a trigger signal and send it to the control module 105; the trigger signal is used to trigger the control module 105 to perform an operation of determining a target control signal, and the current adjustment module 103 automatically generates a compensation current based on the target control signal. The operation of triggering the automatic compensation by the trigger signal can be understood as a self-adjustment operation to automatically compensate for the offset.

[0073] It should be noted that, in the embodiment of the present disclosure, the self-adjustment operation may be triggered by a trigger signal. For example, the trigger signal may be a reset signal or an external sampling signal. Fig.14 or Fig.15 As shown, the reset signal can be provided by the power on reset circuit 109 (Power on Reset, POR), that is, when powered on, the power on reset circuit 109 will generate a pulse signal to reset the control module 105, triggering the control module 105 to perform a calibration; or, the user can provide an external sampling signal to actively initiate a self-adjustment operation. In this way, a calibration is performed every time after powering on to ensure that the square circuit 10 can work in the minimum mismatch state every time after powering on. Fig.14 or Fig.15 As shown, the trigger module 108 can be implemented by an OR gate 1081, and the OR gate 1081 is used to combine two high-level pulses. If other types of reset signals are used, the combinational logic here can also be modified as needed. This process can be implemented by hardware or by software. For software implementation, additional execution units and memories are required for executing and storing code.

[0074] It should also be noted that, since the mismatch is related to temperature, the temperature may change as the square circuit 10 works. In the embodiment of the present disclosure, the control module 105 can obtain the current temperature from the temperature sensor 107 periodically or in real time to find the corresponding target control signal in the storage module 106 to determine the compensation current without a trigger signal to trigger the self-adjustment operation. At this time, the trigger module 108 may not be required in the square circuit 10. Alternatively, it can also be combined with the trigger module 108 to perform calibration when the chip is powered on or manually triggered, and there is no specific limitation on this.

[0075] In some embodiments, when the chip temperature changes significantly after power-on, a calibration is triggered. Fig.16 As shown, in some embodiments, the trigger module 108 is further connected to the temperature sensor 107 to generate a trigger signal when the difference between the current temperature and the last detected temperature is greater than a preset temperature threshold.

[0076] It should be noted that if the self-adjustment operation is triggered only once when the power is turned on, then as the working time increases, the device will heat up seriously, causing the temperature to rise, and the ambient temperature outside the chip will also change, and the circuit mismatch may also change at different temperatures. Therefore, the embodiment of the present disclosure can also perform a self-adjustment operation only when the temperature changes greatly, and re-determine the corresponding most appropriate target control signal according to the current temperature to ensure that effective current compensation is performed in time when the mismatch changes.

[0077] For example, Fig.16 As shown, the trigger module 108 may also include a trigger signal generating module 1082, which is connected to the temperature sensor 107 and the OR gate 1081 respectively. The temperature sensor 107 collects the current temperature in real time or periodically and sends it to the trigger signal generating module 1082. The trigger signal generating module 1082 compares the current temperature value with the previous temperature value. If the difference between the two (taking the absolute value) is greater than the preset temperature threshold, it means that the two temperatures are very different and need to be re-self-adjusted. Then, a trigger signal is output, and the trigger control module 105 performs a self-adjustment operation to determine a new target control signal to ensure that the target control signal meets the current temperature requirement. At the same time, the trigger signal generating module 1082 can also receive the signal output by the OR gate 1081, and perform a trigger operation when either the reset signal or the external sampling signal is enabled.

[0078] It should also be noted that the temperature sensor 107 can provide the temperature to the control module 105 and the trigger signal generating module 1082 through the same port, or as shown in FIG. Fig.16 As shown, the control module 105 and the trigger signal generating module 1082 may also be connected via two ports respectively, and this is not specifically limited.

[0079] In some embodiments, the trigger module 108 is not limited to Fig.16 As shown in the structure, for example, the OR gate 1081 may include three input terminals, which respectively receive a reset signal, an external sampling signal, and a temperature reset signal sent by the trigger signal generating module 1082. The temperature reset signal is used to indicate that the difference between the current temperature and the last detected temperature is greater than a preset temperature threshold.

[0080] In short, the trigger signal (or RST signal) of the control module 105 is generated by two situations: 1. External input, that is, generated by the power-on reset circuit 109 when powered on, or manually generated externally. When the trigger signal generating module 1082 receives such a signal, it will immediately output a trigger signal to the control module 105 to perform a self-adjustment operation. That is, this triggering mode is that when powered on, the power-on reset circuit 109 automatically generates a reset signal to trigger the execution of a self-adjustment, or an external sampling signal requires the execution of a self-adjustment.

[0081] 2. Internal generation of the trigger signal generating module 1082: The trigger signal generating module 1082 will periodically check the current temperature output by the temperature sensor 107. When the current temperature is significantly different from the temperature recorded last time, that is, the temperature has changed significantly, the trigger signal generating module 1082 will generate a trigger signal to the control module 105 to make it perform self-adjustment again. At the same time, the trigger signal generating module 1082 will record the current temperature.

[0082] The aforementioned temperature triggering, reset signal triggering, and external sampling signal triggering self-adjusting operation methods may adopt only one of them, or two of them, or all three of them; and / or, the embodiment of the present disclosure may also periodically and spontaneously perform self-adjusting operations to compensate for the mismatch of the square circuit 10, without specific limitation.

[0083] In some embodiments, Fig.16 As shown, a first switch S1 may be connected between the input end of the square unit 101 and the input end of the AC signal, and a second switch S2 may be connected between the input end of the mirror square unit 102 and the feedback signal input end. During the operation of obtaining the corresponding relationship, the control module 105 generates an input control signal in a non-enabled state, and disconnects both the first switch S1 and the second switch S2. At this time, the AC signal (RF signal) will not be sent to the square unit 101, which can avoid affecting the operation result; after the operation is completed, the control module 105 outputs an input control signal in an enabled state, and turns on the first switch S1 and the second switch S2 again, so that the AC signal (RF signal) can be squared.

[0084] In some embodiments, Fig.16 As shown, the control module 105 is further used to generate and output an invalid indication signal during the operation of obtaining the corresponding relationship, and the invalid indication signal is used to indicate that the output of the square circuit 10 is invalid.

[0085] For example, the target control signal corresponding to each temperature can be determined by a test operation, so the indication signal for obtaining the corresponding relationship can be a test state indication signal, and the operation for obtaining the corresponding relationship can be a test operation. When receiving the test state indication signal, the control module 105 performs the test operation.

[0086] The test operation is usually performed in advance, and at this time, the test operation can be triggered by the test status indication signal. In this case, after the test operation, the target control signal corresponding to the temperature will be stored in the storage module 106. When the temperature changes, the corresponding target control signal (i.e., self-adjustment operation) is searched in the storage module 106 to determine the compensation current, and the self-adjustment operation can be triggered without a trigger signal, that is, the trigger module 108 can be omitted. Alternatively, it can also be combined with the trigger module 108 to trigger the self-adjustment when the chip is powered on or manually, so as to avoid the mismatch changing after a certain working time limit, and the stored target control signal is not effective.

[0087] In this solution, a control method of the square circuit 10 is also provided, including: Get the current temperature; A search is performed in the storage module 106 according to the current temperature to obtain a target control signal, and the target control signal is output to the current adjustment module 103 to compensate for the difference between the first signal and the second signal, thereby eliminating (or at least partially eliminating) the inaccuracy caused by the mismatch between the square unit 101 and the mirror square unit 102.

[0088] The control method can be executed by the control module 105, which can be implemented by software or hardware. In some embodiments, the control module 105 includes a processor and a memory; the processor is used to execute instructions stored in the memory so that the control module 105 executes the aforementioned control method. It should be noted that the control module 105 can be a digital circuit or a logic circuit, which is not specifically limited.

[0089] It should also be noted that the self-regulation method of this solution also includes the step of establishing a corresponding relationship between the temperature and the target control signal, which can be specifically: When there is no AC signal input, at each temperature: Outputting an initial control signal to the current adjustment module 103, the initial control signal being used to control the magnitude of the compensation current; Under the initial control signal, a voltage difference between the output terminals of the square unit 101 and the mirror square unit 102 is obtained; By traversing different initial control signals, determining the initial control signal corresponding to the minimum voltage difference as the target control signal; All temperatures are traversed to obtain corresponding relationships between all temperatures and target control signals, and the corresponding relationships are stored in the storage module 106 .

[0090] In the embodiment of the present disclosure, the self-regulation operation is implemented based on the correspondence between the temperature and the target control signal stored in the storage module 106, without interrupting the normal operation of the square circuit 10. Specifically, the control module 105 is configured to perform an operation of determining the target control signal, including: The control module 105 obtains the current temperature; for example, the control module 105 may obtain the current temperature from the temperature sensor 107; The control module 105 searches the storage module 106 according to the current temperature to obtain a target control signal, and outputs a target control signal corresponding to the current temperature to the current adjustment module 103 . The target control signal is used to control the current adjustment module 103 to output a compensation current of appropriate size.

[0091] It should be noted that the control signal stored in the storage module 106 is recorded as a target control signal, and each temperature value or range corresponds to a target control signal. For example, 256 different temperatures and target control signals corresponding to each temperature are preset, and the 256 temperatures and corresponding target control signals are stored in the storage module 106. Then, when performing the self-adjustment operation, the current temperature is first determined, and then the current temperature is compared with the 256 temperatures stored in the storage module 106 to determine which temperature the current temperature matches, that is, which temperature the current temperature is closest to (equal, or the difference between the two is less than a certain temperature error threshold), and then the target control signal corresponding to the matched temperature is output to the current adjustment module 103, and the current adjustment module 103 outputs the compensation current accordingly. Among them, the current temperature can be detected by the temperature sensor 107. If the temperature range corresponds to the target control signal, it is only necessary to determine in which range the current temperature value is located and output the corresponding target control signal. When the temperature is the current temperature, calibration can be achieved without interrupting the normal operation of the square circuit 10.

[0092] To Fig.16 The circuit shown is calibrated as an example. Fig.17 As shown, the process may include: S401: The control module 105 determines whether it is in a testing state according to a test state indication signal.

[0093] If the judgment result is yes, steps S402 to S4012 (ie, test operation) are executed; otherwise, steps S4013 to S4016 (ie, self-adjustment operation) are executed.

[0094] Before step S402 , the squaring circuit 10 may be placed at a first preset temperature to find a target control signal corresponding to the first preset temperature.

[0095] S402: the control module 105 resets the initial control signal and the optimal voltage difference. The initial control signal is output to the current adjustment module 103 to be used for testing to obtain corresponding target control signals at different temperatures.

[0096] It should be noted that the control signal can be a multi-bit signal. At the beginning of the test, the initial control signal and the optimal voltage difference need to be reset, which is equivalent to initialization. The reset initial control signal and the optimal voltage difference can both be default initial values, which serve as the basis for comparison in step S407.

[0097] Alternatively, the reset initial control signal is the first initial control signal traversed. For example, assuming that the control module 105 can output 100 initial control signals, C1, C2, C3, ..., C100, during the test process, it is necessary to traverse these 100 initial control signals, and the initial control signal that minimizes the voltage difference between the output ends of the square unit 101 and the mirror square unit 102 when there is no AC signal input is determined as the initial control signal. Any one of the 100 initial control signals can be determined as the reset initial control signal. For example, the traversal can be performed in the order of C1 to C100, and C1 can be first determined as the initial control signal reset in this step, or in other orders, without limitation.

[0098] Among them, the optimal voltage difference represents the minimum voltage difference between the output ends of the square unit 101 and the mirror square unit 102 when there is no AC signal input in the initial control signal that has been traversed. Before entering the test state and before starting to adjust based on the initial control signal, the reset optimal voltage difference can be a default value or a voltage difference detected before adjustment.

[0099] S403: The control module 105 waits for a trigger signal. If a trigger signal is received, the process proceeds to step S404. The trigger signal at this time may be triggered by an external sampling signal controlled manually.

[0100] S404: The control module 105 controls ADC2 to sample, and the reading result is recorded as VA.

[0101] S405: The control module 105 controls ADC3 to sample, and the reading result is recorded as VB.

[0102] It should be noted that after being triggered, the control module 105 will send a reset initial control signal to the current adjustment module 103. The current adjustment module 103 performs current compensation based on the received control signal, controls the second analog-to-digital converter 1042 (ADC2) to collect the voltage value of the first signal, and records it as VA; and controls the third analog-to-digital converter 1043 (ADC3) to collect the voltage value of the second signal, and records it as VB.

[0103] S406: The control module 105 calculates the voltage difference |VA-VB|.

[0104] It should be noted that the voltage difference here is the absolute value of VA and VB.

[0105] S407: The control module 105 determines whether the voltage difference is less than the optimal voltage difference.

[0106] If the judgment result is yes, it means that the compensation effect of the current initial control signal is worse than the previously tested initial control signal, and then execute step S408; otherwise, it means that the compensation effect of the current initial control signal is not as good as the previously tested initial control signal, and then execute step S409.

[0107] S408: The control module 105 records the current initial control signal and voltage difference as the target control signal and the optimal voltage difference respectively.

[0108] S409: The control module 105 outputs an initial control signal to the DAC in a step-by-step manner.

[0109] It should be noted that if the initial control signals are output one by one in order from small to large, the next initial control signal is outputted in a step-increase manner according to the corresponding step value; if the initial control signals are output one by one in order from large to small, the next initial control signal is outputted in a step-decrease manner according to the corresponding step value; or, the initial control signals may be outputted in other pre-set orders or any order, and no specific limitation is made thereto. Here, taking the step-increase as an example, for example, the aforementioned 100 initial control signals C1 to C100 increase in sequence, and the difference between two adjacent initial control signals is the step value, then after traversing C1, the next traversal is C2.

[0110] S4010: The control module 105 determines whether the initial control signal exceeds the maximum value.

[0111] If the judgment result is yes, step S4011 is executed, indicating that the target control signal corresponding to the first preset temperature is found; otherwise, the process returns to step S404.

[0112] For example, among the 100 initial control signals C1 to C100 that increase in sequence, the maximum value of the initial control signal is C100. If the initial control signal sent is C101, the maximum value is exceeded.

[0113] S4011: The control module 105 obtains the current temperature from the temperature sensor 107.

[0114] S4012 : The control module 105 writes the current temperature and the target control signal into the storage module 106 .

[0115] Afterwards, the square circuit 10 can be placed at a second preset temperature so that there is a second initial voltage difference between the first signal and the second signal; then steps S402 to S4012 are performed to find the target control signal corresponding to the second initial voltage difference. Similarly, the square circuit 10 is placed at all preset temperatures, the target control signals corresponding to all temperatures are found, and the corresponding relationship between the temperature and the target control signal is obtained.

[0116] It should be noted that the current temperature can be stored in the form of a temperature code.

[0117] S4013 : The control module 105 reads all temperatures and target control signals in the storage module 106 .

[0118] S4014: The control module 105 obtains the current temperature from the temperature sensor 107.

[0119] S4015: The control module 105 calculates the target control signal corresponding to the current temperature.

[0120] S4016: The control module 105 latches and outputs the calculated target control signal to the DAC (digital-to-analog converter 1031), thereby obtaining a target control signal corresponding to the current temperature, and sending it to the current adjustment module 103 to control the current adjustment module 103 to output a compensation current to compensate for the mismatch between the square unit 101 and the mirror square unit 102.

[0121] In short, when the chip is tested before leaving the factory, the test state indication signal is pulled high to enter the test state. At this time, the external sampling signal is no longer a reset function, but it can still be a pulse. Through the cooperation of the test system host computer, an external sampling signal is sent to the chip every time the test environment temperature is changed. When the chip receives the sampling signal, it will perform a self-adjustment operation process, and obtain the current temperature from the temperature sensor 107, and both are recorded in the storage module 106.

[0122] The host computer can perform self-adjustment according to a certain temperature step, such as sending an external sampling signal every time the chip temperature changes by 10°C. After the calibration is completed, when the chip is used normally, the test status indication signal is pulled low, the test state is exited, and the normal working state is entered. The control module 105 will read all the temperatures and target control signals in the storage module 106. After that, the current temperature is read from the temperature sensor 107 in a certain frequency cycle, and the compensation circuit control code required for the current temperature point is confirmed by the interpolation method based on the previously recorded discrete multi-temperature point data, and latched and output to the DAC. Thereby achieving mismatch compensation that changes with temperature.

[0123] Fig.17 The method shown is a specific embodiment of the present invention. In other embodiments, the specific implementation process of the control method is not limited to Fig.17 For example, Fig.14 The circuit shown is calibrated when Fig.17 Steps S404~S405 can be replaced by: The control module 105 controls the switch unit SW to be connected to the port A.

[0124] It should be noted that, before this, the step of outputting an initial control signal to the current adjustment module 103 is also included.

[0125] The control module 105 controls ADC1 to sample, reads the sampling result, and records it as VA.

[0126] The control module 105 controls the switch unit SW to connect to the port B.

[0127] The control module 105 controls ADC1 to sample, reads the sampling result, and records it as VB.

[0128] The above description is only a preferred embodiment of the present disclosure and is not intended to limit the protection scope of the present disclosure.

[0129] It should be noted that in the present disclosure, the terms "include", "comprises" or any other variants thereof are intended to cover non-exclusive inclusion, so that a process, method, article or device including a series of elements includes not only those elements, but also includes other elements not explicitly listed, or also includes elements inherent to such process, method, article or device. In the absence of further restrictions, an element defined by the sentence "includes a ..." does not exclude the existence of other identical elements in the process, method, article or device including the element.

[0130] The serial numbers of the above-mentioned embodiments of the present disclosure are only for description and do not represent the advantages or disadvantages of the embodiments.

[0131] The methods disclosed in several method embodiments provided in the present disclosure can be arbitrarily combined without conflict to obtain new method embodiments.

[0132] The features disclosed in several product embodiments provided in the present disclosure can be arbitrarily combined without conflict to obtain new product embodiments.

[0133] The features disclosed in several method or device embodiments provided in the present disclosure may be arbitrarily combined without conflict to obtain new method embodiments or device embodiments.

[0134] The above description is only a specific implementation mode of the present disclosure, but the protection scope of the present disclosure is not limited thereto. Any technician familiar with the technical field can easily think of changes or substitutions within the technical scope disclosed in the present disclosure, which should be included in the protection scope of the present disclosure.

Claims

1. A self-adjustable square circuit, characterized in that: include: A squaring unit, used to square the received AC signal, the squaring unit receiving a bias voltage and the AC signal, and an output end of the squaring unit outputting a first signal; A mirror square unit, used for receiving the bias voltage, wherein the structure of the mirror square unit is consistent with the structure of the square unit, and the output end of the mirror square unit outputs a second signal; Temperature sensor, used to detect the current temperature; a current adjustment module, configured to receive a target control signal and generate a compensation current, wherein the magnitude of the compensation current is related to the target control signal, wherein an output end of the current adjustment module is connected to an output end of the square unit or the mirror square unit, and is configured to compensate for a difference between the first signal and the second signal; wherein the target control signal is obtained by the control module by looking up a table in the storage module based on the current temperature; The storage module is used to store the corresponding relationship between the temperature and the target control signal.

2. The squaring circuit according to claim 1, characterized in that: When the current adjustment module outputs the compensation current based on the target control signal, the difference between the first signal and the second signal is minimum, zero or substantially zero.

3. The squaring circuit according to claim 1, characterized in that: The squaring circuit further comprises a voltage acquisition module connected to the output ends of the squaring unit and the mirror squaring unit respectively; The control module is further configured to: When there is no AC signal input, at each of the above temperatures: Outputting an initial control signal to the current adjustment module, wherein the initial control signal is used to control the magnitude of the compensation current; Under the initial control signal, obtaining a voltage difference between output terminals of the square unit and the mirror square unit; By traversing different initial control signals, determining the initial control signal corresponding to the minimum voltage difference as the target control signal; All the temperatures are traversed to obtain corresponding relationships between all the temperatures and the target control signals, and the corresponding relationships are stored in the storage module.

4. The squaring circuit according to claim 3, characterized in that: The squaring circuit further includes a first switch and a second switch, wherein the first switch is located between an input terminal of the squaring unit and an input terminal of the AC signal, and the second switch is located between an input terminal of the mirror squaring unit and an input terminal of a feedback signal; The control module is further configured to disconnect the first switch and the second switch during the operation of obtaining the corresponding relationship.

5. The squaring circuit according to claim 3, characterized in that: The control module is further configured to generate and output an invalid indication signal during the execution of the operation of obtaining the corresponding relationship, wherein the invalid indication signal is configured to indicate that the output of the square circuit is invalid.

6. The squaring circuit according to any one of claims 1 to 5, characterized in that: The squaring circuit further comprises: The trigger module is used to receive a reset signal and / or an external sampling signal, and when any one of the reset signal and the external sampling signal is in an enabled state, output a trigger signal and send it to the control module; the trigger signal is used to trigger an operation of determining the target control signal.

7. The squaring circuit according to claim 6, characterized in that: The trigger module is further configured to generate the trigger signal when the difference between the current temperature and the last detected temperature is greater than a temperature threshold.

8. The squaring circuit according to claim 1, characterized in that: The current adjustment module comprises: A digital-to-analog converter, used for receiving the target control signal, performing digital-to-analog conversion on the target control signal, and obtaining a current control signal; The first current source is used to receive the current control signal and generate the compensation current based on the current control signal, wherein the output end of the first current source is connected to the output end of the square unit or the mirror square unit.

9. The squaring circuit according to claim 1, characterized in that: The current adjustment module comprises: A voltage providing unit, configured to provide a first voltage; The resistance adjustment unit is connected to the first voltage and receives the target control signal, changes the resistance value based on the target control signal, and outputs the compensation current.

10. The squaring circuit according to claim 1, characterized in that: The current adjustment module comprises: A second current source receives a second voltage and generates a first current; A current control circuit receives the first current and outputs the compensation current; the current control circuit adjusts the magnitude of the compensation current based on the target control signal.

11. The squaring circuit according to any one of claims 1 to 5 and 8 to 10, characterized in that: The squaring circuit further includes a third current source; an output end of the current adjustment module is connected to an output end of one of the squaring unit and the mirror squaring unit, and an output end of the third current source is connected to an output end of the other of the squaring unit and the mirror squaring unit; The third current source is used to provide a fixed current.

12. The squaring circuit according to any one of claims 1 to 5 and 8 to 10, characterized in that: The squaring circuit includes at least two current adjustment modules for generating at least two compensation currents; the control module obtains at least two control signals based on the current temperature; the output end of one of the current adjustment modules is connected to the output end of one of the squaring unit and the mirror squaring unit, and the output end of the other current adjustment module is connected to the output end of the other of the squaring unit and the mirror squaring unit.

13. The squaring circuit according to any one of claims 3 to 5, characterized in that: The voltage acquisition module includes a first analog-to-digital converter and a switch unit; One end of the switch unit is connected to the first analog-to-digital converter, and the other end is selectively connected to the output end of the square unit or the output end of the mirror square unit; The first analog-to-digital converter is used to perform analog-to-digital conversion on the voltage at the output end of the square unit or the mirror square unit, and output the converted digital signal to the control module.

14. The squaring circuit according to any one of claims 3 to 5, characterized in that: The voltage acquisition module includes a second analog-to-digital converter and a third analog-to-digital converter; The second analog-to-digital converter is connected to the output end of the square unit, performs analog-to-digital conversion on the voltage at the output end of the square unit, and outputs the converted voltage to the control module; The third analog-to-digital converter is connected to the output end of the mirror square unit, performs analog-to-digital conversion on the voltage at the output end of the mirror square unit, and outputs the converted voltage to the control module.

15. A method for controlling a square circuit, characterized in that: Applied to the squaring circuit according to any one of claims 1 to 14, the method comprising: Get the current temperature; A search is performed in the storage module according to the current temperature to obtain a target control signal, and the target control signal is output to the current adjustment module; wherein the storage module stores a corresponding relationship between the temperature and the target control signal.

16. The method according to claim 15, characterized in that The method further comprises: When there is no AC signal input, at each of the above temperatures: Outputting an initial control signal to the current adjustment module, wherein the initial control signal is used to control the magnitude of the compensation current; Under the initial control signal, obtaining a voltage difference between output terminals of the square unit and the mirror square unit; By traversing different initial control signals, determining the initial control signal corresponding to the minimum voltage difference as the target control signal; All the temperatures are traversed to obtain corresponding relationships between all the temperatures and the target control signals, and the corresponding relationships are stored in the storage module.

17. A control module, characterized in that: including a processor and a memory; The processor is used to execute instructions stored in the memory so that the control module executes the control method as claimed in claim 15 or 16.

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