Charge control method, charge control circuit, and electronic device

Abstract

The application discloses a charge control method, a charge control circuit and an electronic device. The charge control method is applied to charge control of a multiphase voltage conversion circuit. The multiphase voltage conversion circuit comprises a set number of switching sub-circuits. The charge control method comprises the following steps: obtaining a pulse reference current and a power supply characteristic parameter of the multiphase voltage conversion circuit; in response to a rising edge of the pulse reference current, generating a set number of driving control signals by using the set number, the pulse reference current and the power supply characteristic parameter; wherein a first rising edge of each driving control signal is synchronous; phase-modulating each driving control signal by using the set number and a preset switching period; and sending each phase-modulated driving control signal to each switching sub-circuit respectively, so as to trigger each switching sub-circuit to change a switching state respectively. In the above manner, the charge control method can simultaneously consider a faster rising time of an output current and avoid the occurrence of overshoot.

Description

TECHNICAL FIELD

[0001] The present application relates to the technical field of circuit control, in particular to a charge control method, a charge control circuit and an electronic device. BACKGROUND

[0002] Nowadays, with the increasing richness of electronic devices, the performance requirements of the driving power supply of the electronic devices are increasingly stringent, especially for the switching constant current source, which is a technical difficulty for the high requirements of the rising time, the falling time and the overshoot. Common switching constant current sources mostly use BUCK converter (buck converter) or BOOST converter (boost converter) as the basic circuit structure. For the BUCK converter and the BOOST converter, in order to make the output current rising time short enough, the duty cycle needs to be as large as possible in the output current rising stage to ensure that the rising speed is fast enough.

[0003] However, using the conventional PI (Proportional Integral, proportional and integral) closed-loop control, in order to make the duty cycle large enough when the rising edge comes, the PI parameters needed will be large, which is beneficial to the optimization of the rising time, but at the same time it will bring the problem of large overshoot, so it is impossible to simultaneously consider the contradiction between the output current rising time and the overshoot in the PI closed-loop control loop. SUMMARY

[0004] The technical problem solved by the present application is to provide a charge control method, a charge control circuit and an electronic device, which can solve the problem that the charge control method in the related art cannot simultaneously consider the contradiction between the output current rising time and the overshoot in the PI closed-loop control loop.

[0005] To solve the above technical problem, one technical solution adopted by the present application is to provide a charge control method applied to charge control of a multi-phase voltage conversion circuit, the multi-phase voltage conversion circuit including a set number of switching sub-circuits, the set number being greater than 1, wherein the charge control method includes: obtaining a pulse reference current and a power supply characteristic parameter of the multi-phase voltage conversion circuit; in response to a rising edge of the pulse reference current, generating a set number of driving control signals by using the set number, the pulse reference current and the power supply characteristic parameter; wherein a first rising edge of each driving control signal is synchronous; phase-modulating each driving control signal by using the set number and a preset switching period; and sending each phase-modulated driving control signal to each switching sub-circuit to trigger each switching sub-circuit to change the switching state, respectively.

[0006] The power supply characteristic parameters include input voltage, output voltage, output current, equivalent inductance and preset adjustment coefficient, the drive control signals include first control signals and second control signals, in response to rising edges of the pulse reference currents, the step of generating the set number of drive control signals by using the pulse reference currents and the power supply characteristic parameters includes: in response to the rising edge of each pulse reference current, a reference turn-on time is obtained by using the input voltage, the output voltage, the pulse reference current, the set number, the equivalent inductance and the preset adjustment coefficient; the set number of first control signals is generated by using the reference turn-on time; wherein rising edges of the first control signals are synchronous; the second control signals are generated by using a difference between the pulse reference current and the output current until the rising edge of the next pulse reference current.

[0007] The step of adjusting the phase of each drive control signal by using the set number and the preset switching period includes: adjusting a phase difference between falling edges of each adjacent two first control signals to a quotient of the preset switching period divided by the set number, and making a sum of turn-on times of the first control signals equal to a product between the reference turn-on time and the set number.

[0008] The step of generating the second control signals by using the difference between the pulse reference current and the output current includes: in response to the falling edge of each first control signal, the second control signals are generated by using the difference between the pulse reference current and the output current after a delay for a set time length.

[0009] The step of obtaining the reference turn-on time by using the input voltage, the output voltage, the pulse reference current, the set number, the equivalent inductance and the preset adjustment coefficient includes: the reference turn-on time is obtained by calculating the input voltage, the output voltage, the pulse reference current, the set number, the equivalent inductance and the preset adjustment coefficient by using a preset adjustment function; wherein the preset adjustment function is:

[0010] tj= ;

[0011] Wherein, tj is the reference turn-on time, is the pulse reference current, is the preset adjustment coefficient, n is the set number, is the input voltage, is the output voltage, is the equivalent inductance.

[0012] The supply characteristic parameter further includes an input current, and the step of generating the second control signal by using the difference between the pulse reference current and the output current includes: performing proportional integral adjustment on the current difference between the pulse reference current and the output current to obtain a target current integral value; performing energy storage integral adjustment on the input current to obtain an integral voltage value; obtaining an integral reference value by using the difference between a given reference voltage and the integral voltage value; and obtaining the second control signal by using the target current integral value and the integral reference value.

[0013] The supply characteristic parameter includes an output current, and the step of generating the set number of drive control signals by using the pulse reference current and the supply characteristic parameter includes: performing proportional integral adjustment on the current difference between the pulse reference current and the output current to obtain a target current integral value; and obtaining the set number of drive control signals by using the target current integral value.

[0014] In the step of obtaining the set number of drive control signals by using the target current integral value, the method further includes: detecting whether the current difference is less than a set current threshold value; if the current difference is less than the set current threshold value, multiplying the target current integral value by a set multiple; wherein the set multiple is less than 1 and greater than 0; or multiplying a duty cycle of the drive control signal by the set multiple.

[0015] The step of adjusting the phase of each drive control signal by using the set number and a preset switching period includes: in the switching period of each drive control signal, gradually adjusting the phase difference between each adjacent two drive control signals by using a preset positive correlation function until the phase difference between each adjacent two drive control signals is a quotient of the preset switching period divided by the set number.

[0016] To solve the above technical problems, another technical solution adopted by the present application is to provide a charge control circuit, wherein the charge control circuit is coupled to a multiphase voltage conversion circuit; wherein the charge control circuit uses the charge control method as described in any one of the above to control the charge of the multiphase voltage conversion circuit.

[0017] To solve the above technical problems, another technical solution adopted by the present application is to provide an electronic device, wherein the electronic device includes a housing and a charge control circuit connected to the housing; wherein the charge control circuit is the charge control circuit as described above.

[0018] The beneficial effects of the present application are: Different from the prior art, the charge control method provided by the present application acquires the pulse reference current and the power supply characteristic parameter of the multi-phase voltage conversion circuit, generates a set number of driving control signals by using the set number, the pulse reference current and the power supply characteristic parameter in response to the rising edge of the pulse reference current, and synchronizes the first rising edge of each driving control signal, so as to trigger the simultaneous conduction of each switch sub-circuit by using each driving control signal, effectively improve the rising speed of the output current, significantly reduce the rising time of the output current, and phase-modulate each driving control signal by using the set number and the preset switching period, so as to gradually stagger the conduction of each switch sub-circuit, which can also effectively avoid the possible overshoot problem, so as to simultaneously consider the faster rising time of the output current and avoid the occurrence of overshoot. BRIEF DESCRIPTION OF DRAWINGS

[0019] In order to more clearly illustrate the technical solutions in the embodiments of the present application, the drawings needed in the embodiment description will be briefly introduced. Obviously, the drawings in the following description are only some embodiments of the present application, and other drawings can be obtained by those skilled in the art without creative labor on the basis of these drawings.

[0020] Figure 1 is a flowchart of the first embodiment of the charge control method of the present application;

[0021] Figure 2 is a structural schematic diagram of the first embodiment of the charge control circuit of the present application;

[0022] Figure 3 is Figure 1 is a flowchart of an embodiment of S12 in the present application;

[0023] Figure 4 is a structural schematic diagram of the second embodiment of the charge control circuit of the present application;

[0024] Figure 5 is Figure 3 is a waveform schematic diagram of an embodiment of each related signal in the charge control method in the present application;

[0025] Figure 6 is Figure 3 is a waveform schematic diagram of an embodiment of each related signal in the charge control method under different load states in the present application;

[0026] Figure 7 is Figure 3 is a flowchart of an embodiment of S123 in the present application;

[0027] Figure 8 is Figure 6 is a logic framework diagram of signal processing in the charge control method in the present application;

[0028] Figure 9 is a flowchart of a second embodiment of the charge control method of the present application;

[0029] Figure 10 is Figure 9 is a waveform diagram of an embodiment of each relevant signal in the charge control method;

[0030] Figure 11 is a structural diagram of an embodiment of the electronic device of the present application. DETAILED DESCRIPTION

[0031] The technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application. Obviously, the described embodiments are only part of the embodiments of the present application, rather than all the embodiments of the present application. Based on the embodiments in the present application, all other embodiments obtained by those skilled in the art without creative work fall within the scope of protection of the present application.

[0032] The terms "first", "second", "third" in the present application are only for descriptive purposes, and cannot be understood as indicating or implying relative importance or implicitly indicating the number of the indicated technical features. Therefore, the features defined with "first", "second", "third" can explicitly or implicitly include at least one of the features. In the description of the present application, the meaning of "multiple" is at least two, such as two, three, etc., unless otherwise explicitly and specifically limited. All directional indications (such as up, down, left, right, front, back, etc.) in the embodiments of the present application are only used to explain the relative position relationship, movement condition, etc. between the components in a certain posture (as shown in the drawings), and if the certain posture changes, the directional indications also change accordingly. In addition, the terms "include" and "have" and any variations thereof are intended to cover non-exclusive inclusion. For example, a process, method, system, product or device that includes a series of steps or units is not limited to the listed steps or units, but can optionally include steps or units not listed, or can optionally include other steps or units inherent to the process, method, product or device.

[0033] In this document, the term "embodiment" means that a particular feature, structure, or characteristic described in connection with the embodiment can be included in at least one embodiment of the present application. The appearance of this phrase in various places in the specification does not necessarily all refer to the same embodiment, nor is it necessarily mutually exclusive of other embodiments. It is explicitly and implicitly understood that the embodiments described herein can be combined with other embodiments.

[0034] The present application will be described in detail below with reference to the drawings and embodiments.

[0035] Please refer to Figure 1 and Figure 2 wherein, Figure 1 is a flowchart of the charge control method of the first embodiment of the present application, Figure 2 is a structural schematic diagram of the charge control circuit of the first embodiment of the present application. Specifically, it can include the following steps:

[0036] S11: obtaining a pulse reference current and a power supply characteristic parameter of a multi-phase voltage conversion circuit.

[0037] It can be understood that the charge control method in the embodiment is specifically applied to the charge control of the first multi-phase voltage conversion circuit 30 as shown in the figure. Figure 2 The first charge control circuit 20 implements charge control on the first multi-phase voltage conversion circuit 30 by using the charge control method described in any one of the embodiments.

[0038] The first multi-phase voltage conversion circuit 30 specifically includes a set number n of switching sub-circuits, and the set number n is a positive integer greater than 1.

[0039] It is worth noting that the first multi-phase voltage conversion circuit 30 can specifically be a multi-phase parallel interleaved BUCK circuit, or a multi-phase parallel interleaved BOOST circuit, or any other reasonable circuit topology, and the present embodiment does not limit this.

[0040] In some embodiments, the first charge control circuit 20 can specifically include one of any reasonable circuit unit with signal processing function, such as a control chip, a DSP (Digital Signal Processing) chip, an MCU (Micro Controller Unit) circuit, a CPU (Central Processing Unit), a single-chip microcomputer, a field programmable gate array, a programmable logic device, a discrete gate or transistor logic device, and a discrete hardware, etc.

[0041] In addition, "coupling" in the present embodiment refers to including any direct and indirect connection means. Therefore, if the first circuit is described as being coupled to the second circuit in the text, it means that the first circuit can be directly connected to the second circuit through electrical connection or wireless transmission, optical transmission, etc. Signal connection method, or indirectly electrically connected or signal connected to the second circuit through other circuits or connection means.

[0042] Specifically, the first charge control circuit 20 monitors in real time various circuit parameters of the first multiphase voltage conversion circuit 30, such as one or more of any reasonable power supply characteristic parameters, such as input voltage, output current, output voltage, etc., and sets the pulse reference current according to the preset control program, or receives the pulse reference current obtained by experimental calibration or simulation optimization according to the specific working condition and power supply demand of the load circuit by the upper computer.

[0043] The power supply characteristic parameters can be obtained by any reasonable sampling method such as sensors, sampling resistors, experimental calibration, simulation optimization or circuit model estimation, which is not limited in the present application.

[0044] It is worth noting that the upper computer generally refers to a computer system with strong computing and data processing capabilities. It is responsible for monitoring, issuing instructions, data acquisition, processing and analysis, and user interaction of the entire control system. As the "brain" of the system, it can handle complex algorithms, store long-term data, and provide a graphical interface for user operation.

[0045] The lower computer refers to a device or controller in the control system that is directly connected to sensors, actuators and other hardware. It is responsible for executing specific control instructions issued by the upper computer, such as output of switching signals, adjustment of analog quantities, and acquisition of data. The lower computer usually performs simple logic judgment and real-time control tasks.

[0046] In the present embodiment, the upper computer can be understood as the central controller of the front-end circuit of the first multiphase voltage conversion circuit 30, and the lower computer is the first multiphase voltage conversion circuit 30.

[0047] S12: In response to the rising edge of the pulse reference current, a set number of driving control signals are generated using the set number, the pulse reference current and the power supply characteristic parameters.

[0048] It can be understood that the pulse reference signal is the control target of the current output current of the first multiphase voltage conversion circuit 30, so that when the pulse reference signal is obtained, it indicates that the current output current needs to be adjusted to approach the pulse reference signal. And the pulse reference signal has a transition from low to high, i.e. the rising edge, and a transition from high to low, i.e. the falling edge, so that when the first rising edge is detected, it corresponds to the arrival of the first wave of the pulse reference signal.

[0049] The first charge control circuit 20 is used to identify and detect the rising edge of the pulse reference signal, which can be achieved by any reasonable means such as hardware circuit (such as edge trigger), software algorithm (for example, writing corresponding code in embedded system) or controller counter, which is not limited in the present application.

[0050] and when a rising edge of the pulse reference current is detected, a preset control algorithm or a preset adjustment function is used to operate and process the set number n, the pulse reference current and the power supply characteristic parameter to obtain the set number n of driving control signals.

[0051] The first rising edge of each driving control signal is synchronized, that is, each driving control signal is started at the same time, and the first rising edge corresponds to the same time.

[0052] In some embodiments, the driving control signal can be one or more of a PWM (Pulse Width Modulation) signal or a PFM (Pulse Frequency Modulation) signal, or any reasonable control signal, which is not limited in the present application.

[0053] S13: Phase modulation is performed on each driving control signal using the set number and the preset switching period.

[0054] Further, each driving control signal is phase-modulated in sequence based on the total number of switching sub-circuits, that is, the set number n and the preset switching period, so that each driving control signal is phase-shifted with respect to each other.

[0055] It is worth noting that the preset switching period is the switching period set according to the physical characteristics of each switching sub-circuit, that is, the set period of each driving control signal, which can be a constant value or adjusted as needed, which is not limited in the present application.

[0056] S14: Each phase-modulated driving control signal is sent to each switching sub-circuit to trigger each switching sub-circuit to change the switching state.

[0057] Each phase-modulated driving control signal is sent to each switching sub-circuit to trigger each switching sub-circuit to change the switching state, so as to adjust the output current and output voltage of the first multi-phase voltage conversion circuit 30.

[0058] The above scheme synchronizes the first rising edge of each driving control signal to trigger each switching sub-circuit to conduct at the same time using each driving control signal, which can effectively improve the rising speed of the output current and significantly reduce the rising time of the output current. By phase-modulating each driving control signal using the set number n and the preset switching period, each switching sub-circuit is gradually staggered to conduct, which can effectively avoid the overshoot problem that may occur, so as to simultaneously consider the faster rising time of the output current and avoid the occurrence of overshoot, thereby improving the power supply stability and reliability of the first multi-phase voltage conversion circuit 30, the dynamic response performance is also good, and the control strategy is simplified.

[0059] It is worth mentioning that the overshoot refers to the phenomenon that the controlled parameter temporarily exceeds the set value before the control system reaches the steady state. Specifically, when the system is disturbed, the controlled parameter temporarily exceeds the set value under the action of the regulator, and then returns to the set value. This phenomenon is called overshoot.

[0060] Please continue to refer to Figure 3 , Figure 3 is Figure 1 a flowchart of an embodiment of S12. In an embodiment, the charge control method of the present application further includes some more specific steps in addition to S11-S14. Specifically, S12 can further include the following steps:

[0061] S121: in response to the rising edge of each pulse reference current, the reference turn-on time is obtained using the input voltage, the output voltage, the pulse reference current, the set number, the equivalent inductance, and the preset adjustment coefficient.

[0062] Please continue to refer to Figure 4 and Figure 5 wherein, Figure 4 is a structural schematic diagram of a second embodiment of the charge control circuit of the present application, Figure 5 is Figure 3 a waveform schematic diagram of each related signal of the charge control method in

[0063] It can be understood that the charge control method in the present embodiment can be implemented by the second charge control circuit (not shown in the figure) to the second multiphase voltage conversion circuit 40 as shown in Figure 4 for charge control to supply power to the load circuit 101 using the DC power supply DC. Wherein, the second multiphase voltage conversion circuit 40 includes a switching sub-circuit 41 and a regulation output sub-circuit 42, the number of switching sub-circuits 41 is a set number n (n is a positive integer greater than 1); for the convenience of understanding, here take the set number n as 3 for example, that is, the switching sub-circuit 41 includes the first switch Q1, the second switch Q2 and the third switch Q3, the regulation output sub-circuit 42 includes the first diode D1, the second diode D2, the third diode D3, the first inductor L1, the second inductor L2, the third inductor L3 and the output capacitor C1; the load circuit 101 includes the equivalent diode DF and the equivalent resistor R1.

[0064] The first end of the first switch tube Q1 is coupled to the first end of the second switch tube Q2 and the first end of the third switch tube Q3, and is used to be coupled to the first end of the direct current power supply DC, the second end of the first switch tube Q1 is coupled to the first end of the first inductor L1 and the second end of the first diode D1, the second end of the second switch tube Q2 is coupled to the first end of the second inductor L2 and the second end of the second diode D2, the second end of the third switch tube Q3 is coupled to the first end of the third inductor L3 and the second end of the third diode D3, the second end of the first inductor L1 is coupled to the second end of the second inductor L2, the second end of the third inductor L3, the first end of the output capacitor C1, and is used to be coupled to the first end of the equivalent diode DF, the first end of the first diode D1 is coupled to the first end of the second diode D2, the first end of the third diode D3, the second end of the output capacitor C1, and is used to be coupled to the second end of the direct current power supply DC and the second end of the equivalent resistor R1, the second end of the equivalent diode DF is coupled to the first end of the equivalent resistor R1, the third end of the first switch tube Q1, the third end of the second switch tube Q2 and the third end of the third switch tube Q3 are all coupled to the second charge control circuit.

[0065] In some embodiments, the first switch tube Q1, the second switch tube Q2 and the third switch tube Q3 can be one of a MOSFET (Metal Oxide Semiconductor Field Effect Transistor), a transistor, a thin film transistor or a field effect transistor or any other reasonable switch tube, which is not limited in the present application.

[0066] In other embodiments, the second multi-phase voltage conversion circuit 40 can also be a multi-phase BOOST circuit, or a multi-phase BUCK circuit including 2, 5 or 6 or any other reasonable number of switching sub-circuits 41; and the load circuit 101 can also include one or more of an equivalent series resistor, an equivalent capacitor, an equivalent series diode or any other reasonable circuit element, which is not limited in the present embodiment.

[0067] The power supply characteristic parameter can include an input voltage, an output voltage, an output current Io, an equivalent inductance and a preset adjustment coefficient; and the driving control signal includes a first control signal and a second control signal.

[0068] Specifically, the second charge control circuit detects each rising edge of the pulse reference current in real time, and in response to each rising edge of the pulse reference current, uses a preset control program or a preset adjustment function to perform operation processing on the input voltage, the output voltage, the pulse reference current, the set number n, the equivalent inductance and the preset adjustment coefficient to obtain a reference turn-on time.

[0069] S122: generate a set number of first control signals using the reference turn-on time.

[0070] Further, according to the current acquired reference turn-on time, a set number n of first control signals are generated in sequence, and the rising edges of each first control signal are guaranteed to be synchronized, i.e., the first rising edges of the first driving control signal G1, the second driving control signal G2, and the third driving control signal G3 correspond to the same time, so as to trigger the first switch tube Q1, the second switch tube Q2, and the third switch tube Q3 to conduct at the same time, thereby effectively improving the rising speed of the output current and significantly reducing the rising time of the output current.

[0071] It can be understood that the first driving control signal G1, the second driving control signal G2, and the third driving control signal G3 are the first control signals of the first switch tube Q1, the second switch tube Q2, and the third switch tube Q3, respectively, i.e., the first control signals sent to the first switch tube Q1, the second switch tube Q2, and the third switch tube Q3 when the first wave of the pulse reference current arrives, and can be a set duty cycle, i.e., an open-loop control signal obtained according to the reference turn-on time. When the rising edge of the pulse reference current arrives, the first control signal corresponding to the rising edge synchronization can trigger the first switch tube Q1, the second switch tube Q2, and the third switch tube Q3 to conduct at the same time. At this time, the multiphase inductor currents, i.e., the first inductor current I L1 , the second inductor current I L2 , and the third inductor current I L3 will rise at the same time, and the output current Io will also rise, thereby effectively improving the rising speed of the output current Io and significantly reducing the rising time of the output current Io.

[0072] Please continue to refer to Figure 6 , Figure 6 is Figure 3 a waveform diagram of an embodiment of the charge control method under different load states.

[0073] It can be understood that in the load switching operating condition, i.e., when the amplitude of the pulse reference current changes, the same scheme can also be used to calculate the pulse width of the open-loop wave, i.e., the turn-on time of each first control signal, thereby optimizing the output current Io rising time of the load switching, and the multiphase simultaneous starting optimizes the rising time, and the determination method of the open-loop turn-on time is also simpler.

[0074] S123: generate a second control signal using the difference between the pulse reference current and the output current until the rising edge of the next pulse reference current.

[0075] After the first wave control signal, the current difference between the pulse reference current and the output current Io is obtained, and the second control signal is obtained by proportional integral adjustment or other reasonable operation adjustment of the current difference, until the next rising edge of the pulse reference current is detected again, and the cycle of S121-S123 is repeated.

[0076] It is worth noting that the second control signal can be understood as a closed-loop control signal obtained by current feedback adjustment control loop after the first wave first control signal, that is, the first driving control signal G1, the second driving control signal G2, and the third driving control signal G3 are generated by using current closed-loop control strategy after the first wave control signal of the first switch tube Q1, the second switch tube Q2, and the third switch tube Q3, that is, the first control signal. And reset before another rising edge comes after the pulse reference current falling edge, that is, the corresponding driving control is alternately performed again with the first control signal and the second control signal.

[0077] It can be understood that the first driving control signal G1, the second driving control signal G2, and the third driving control signal G3 are actually generated based on two different control strategies and operation programs, and are obtained by using a specific alternating cycle generation method, that is, the time interval between every two adjacent rising edges of the pulse reference current is used as the cycle control period, and the first control signal and the second control signal are alternately generated by using two different control strategies.

[0078] The second charge control circuit is specifically configured to, in response to each rising edge of the pulse reference current, first calculate the first control signal by using a corresponding preset adjustment function; and the first control signal is the first wave control signal, and after the first control signal, that is, from the second control signal, until the next rising edge of the pulse reference current is detected again, the second control signal is generated according to the corresponding closed-loop feedback control strategy of the current loop, so that the first control signal with the rising edge is used to make the output current have a faster rising time, and the second control signal obtained by using the closed-loop feedback adjustment and out of phase is used to avoid overshoot.

[0079] Therefore, between every two adjacent rising edges of the pulse reference current, the first driving control signal G1, the second driving control signal G2, and the third driving control signal G3 are alternately generated as the first control signal and the second control signal; and the first control signal is the first wave control signal, and after the first control signal, they are all second control signals, until the rising edge of the next pulse reference current, and the first control signal and the second control signal are alternately generated again, and so on. Here, it is not repeated.

[0080] Further, in an embodiment, S121 can specifically include: calculating the input voltage, the output voltage, the pulse reference current, the set number n, the equivalent inductance and the preset adjustment coefficient by using a preset adjustment function to obtain the reference turn-on time tj.

[0081] wherein the preset adjustment function is:

[0082] tj= ;

[0083] wherein tj is the reference turn-on time, is the pulse reference current, is the preset adjustment coefficient, and n is the set number, is the input voltage, is the output voltage, is the equivalent inductance.

[0084] It is worth noting that the ideal turn-on time of the first switch Q1, the second switch Q2 and the third switch Q3 can be calculated, and different ideal turn-on times can be given according to different pulse reference currents. In order to avoid the overshoot problem of the subsequent opening and closing loop connection, the ideal turn-on time can be multiplied by a preset adjustment coefficient to obtain the reference turn-on time tj.

[0085] In addition, the preset adjustment coefficient is specifically a coefficient less than 1 and greater than 0, which is not limited in the present application.

[0086] The equivalent inductance L can be understood as the same equivalent inductance value corresponding to the first inductance L1, the second inductance L2 and the third inductance L3, and the single-phase inductance current rising slope: .

[0087] The rising slope of the output current Io is the number of parallel phases, that is, the set number n multiplied by the rising slope of the single-phase inductance current, so we can get:

[0088] tj= = .

[0089] Further, in an embodiment, S123 can specifically include: in response to the falling edge of each first control signal, delaying for a set time length to generate the second control signal by using the difference between the pulse reference current and the output current Io.

[0090] It can be understood that in one switching cycle, there is a turn-on time and a turn-off time, and the turn-off time also includes an unavoidable dead time, so at the falling edge of each first control signal, after delaying for a specific turn-off time, that is, a set time length, the second control signal is generated by using the difference between the pulse reference current and the output current Io.

[0091] Further, in an embodiment, the S13 can specifically include: adjusting the phase difference between every two adjacent first control signals falling edges to the quotient of the preset switching period T divided by the set number n, and making the sum of the turn-on time of each first control signal equal to the product between the reference turn-on time tj and the set number n.

[0092] It can be understood that, in order to avoid the output current Io drop caused by the simultaneous sealing of multiple phases when the open loop and the closed loop are connected, the sealing cannot be performed at the same time when the open loop is sealed, that is, the falling edges of each first control signal cannot be at the same time. The closed loop feedback regulation can be performed in a direct phase staggered manner, that is, the rising edges of each second control signal are directly phase staggered, and the phase difference between every two adjacent second control signals, that is, corresponding to two adjacent switch tubes, is T / n, where T is the preset switching period.

[0093] Correspondingly, the phase difference between every two adjacent first control signals falling edges needs to be adjusted to the quotient of the reference switching period divided by the set number n, and the sum of the turn-on time of each first control signal is equal to the product between the reference turn-on time tj and the set number n.

[0094] Wherein, when the set number n is 3, in order to ensure that the turn-on time of each first control signal is as evenly distributed as possible, the first turn-on time of the second drive control signal G2 can be specifically equal to the reference turn-on time tj; the first turn-on time of the first drive control signal G1 is the reference turn-on time tj minus T / n; and the first turn-on time of the third drive control signal G3 is the reference turn-on time tj plus T / n.

[0095] And in other embodiments, when the set number n is 4, the first turn-on time of the first drive control signal G1 can be specifically equal to the reference turn-on time tj minus 3T / 2n; the first turn-on time of the second drive control signal G2 is the reference turn-on time tj minus T / 2n; the first turn-on time of the third drive control signal G3 is the reference turn-on time tj plus T / 2n; and the first turn-on time of the fourth drive control signal is the reference turn-on time tj plus 3T / 2n; and so on. The specific turn-on time of each first control signal when the set number n is even and odd can be obtained respectively, which will not be described here.

[0096] It is worth mentioning that when the rising edges of each first control signal are synchronized and the falling edges have a phase difference, each first control signal actually corresponds to different signal waveforms and has different conduction times and signal periods.

[0097] Please continue to refer to Figure 7 , Figure 7 is Figure 3Flowchart of S123 in an embodiment. In an embodiment, the charge control method of the present application further comprises some more specific steps in addition to S121-S123. Specifically, S123 can further comprise the following steps:

[0098] S1231: proportionally and integrally adjust the current difference between the pulse reference current and the output current to obtain a target current integral value.

[0099] Please continue to refer to Figure 8 , Figure 8 is Figure 6 the logic framework diagram of the signal processing in the charge control method.

[0100] Specifically, the pulse reference current Iref is subtracted from the output current Io to obtain a current difference, and the current difference is proportionally and integrally adjusted to obtain a target current integral value.

[0101] S1232: energy storage integral adjustment is performed on the input current to obtain an integral voltage value.

[0102] Further, the first input current Iin1, the second input current Iin2 and the third input current Iin3 are respectively sampled from the first switch Q1, the second switch Q2 and the third switch Q3 to charge the integral capacitors (not shown in the figure) in the second charge control circuit with the first input current Iin1, the second input current Iin2 and the third input current Iin3, so as to obtain the first integral voltage value, the second integral voltage value and the third integral voltage value through integral adjustment.

[0103] S1233: obtain an integral reference value by using the difference between the given reference voltage and the integral voltage value.

[0104] The given reference voltage is set according to the power supply requirement, or the given reference voltage sent by the upper controller is received, so as to subtract the first integral voltage value, the second integral voltage value and the third integral voltage value from the given reference voltage respectively to obtain the first integral reference value, the second integral reference value and the third integral reference value.

[0105] S1234: obtain a second control signal by using the target current integral value and the integral reference value.

[0106] The target current integral value is compared with the first integral reference value, the second integral reference value and the third integral reference value respectively to obtain each second control signal, i.e. the first driving control signal G1, the second driving control signal G2 and the third driving control signal G3 obtained by closed-loop control after the first wave. For example, the moment when the target current integral value is equal to the first integral reference value is determined as the turn-off moment of the first driving control signal G1, i.e. the falling edge, and the rising edge of the first driving control signal G1 is determined according to the preset switching period, and the second driving control signal G2 and the third driving control signal G3 are obtained according to the signal processing logic.

[0107] Please refer to Figure 9 , Figure 9 is a flowchart of the second embodiment of the charge control method of the present application. The charge control method of the present embodiment is a detailed embodiment of the charge control method in Figure 1 , and specifically includes the following steps:

[0108] S51: Obtain the pulse reference current and the power supply characteristic parameters of the multi-phase voltage conversion circuit.

[0109] Please continue to refer to Figure 10 , Figure 10 is a waveform diagram of an embodiment of various related signals of the charge control method in Figure 9

[0110] Specifically, the first charge control circuit 20 monitors and obtains various circuit parameters of the first multi-phase voltage conversion circuit 30 in real time, such as one or more of any reasonable power supply characteristic parameters such as input voltage, output current Io, output voltage, etc., and sets the pulse reference current according to the preset control program, or receives the pulse reference current obtained by experimental calibration or simulation optimization by the upper computer according to the specific working condition and power supply demand of the load circuit.

[0111] The power supply characteristic parameters specifically include the output current Io.

[0112] S52: In response to the rising edge of the pulse reference current, proportionally and integrally adjust the current difference between the pulse reference current and the output current to obtain a target current integral value.

[0113] The first charge control circuit 20 is used to identify and detect the rising edge of the pulse reference signal, so as to subtract the output current Io from the pulse reference current to obtain a current difference when the rising edge of the pulse reference current is detected, and proportionally and integrally adjust the current difference to obtain a target current integral value.

[0114] S53: Detect whether the current difference is less than a set current threshold.

[0115] ​It can be understood that, in order to balance the contradiction between the rising time of the output current Io and the overshoot, a PI parameter variable control strategy can also be used, that is, when the actual output current Io is small, the PI parameters are large, so as to ensure that the duty cycle of the PWM wave is large enough, and the integral part of the PI can be quickly saturated, and when the actual output current Io is close to the pulse reference current, that is, when the current difference is small, the PI parameters need to be reduced to prevent the occurrence of overshoot.

[0116] Specifically, it is detected whether the current difference obtained currently is less than a set current threshold.

[0117] It is worth noting that the set current threshold is a specific current threshold that is reasonably set when the actual output current Io is close to the pulse reference current and there is a risk of overshoot, and is determined by the actual application scenario, which is not limited in the present application.

[0118] If the current difference is less than the set current threshold, S54 is performed, and if the current difference is not less than the set current threshold, S55 is performed.

[0119] S54: multiplying the target current integral value by a set multiple.

[0120] It can be understood that when it is determined that the current difference is less than the set current threshold, the corresponding PI parameters can be reduced to avoid overshoot.

[0121] Specifically, the target current integral value is multiplied by a set multiple.

[0122] In some embodiments, the set multiple is less than 1 and greater than 0, and is preferably 0.5, which is not limited in the present application.

[0123] S55: obtaining a set number of driving control signals using the target current integral value.

[0124] Further, a set number n of driving control signals are obtained in sequence using the adjusted target current integral value.

[0125] It is worth noting that the first charge control circuit 20 can obtain a set number n of driving control signals in sequence by processing the target current integral value using a current loop feedback adjustment control strategy, or can obtain a set number n of driving control signals in sequence using the above-mentioned S1231-S1234 control strategy, which is not limited in the present application.

[0126] S56: in the switching period of each driving control signal, a preset positive correlation function is used to gradually adjust the phase difference between each adjacent two driving control signals until the phase difference between each adjacent two driving control signals is a quotient of a preset switching period divided by a set number n.

[0127] Further, in each switching cycle of the driving control signal, a preset positive correlation function, such as an arithmetic progression function, a linear increasing function or a non-linear increasing function, is adopted to gradually adjust the phase difference between each adjacent two driving control signals, taking the number n as 3 for example, the first rising edge and falling edge of the first driving control signal G1, the second driving control signal G2 and the third driving control signal G3 are synchronized, and the phase of the first driving control signal G1 is kept unchanged, and the preset positive correlation function is respectively adopted to adjust the phase of the second driving control signal G2 and the third driving control signal G3, so that the second driving control signal G2 gradually increases with the first driving control signal G1, and the third driving control signal G3 gradually increases with the second driving control signal G2, until the phase difference between each adjacent two driving control signals, i.e. the phase difference between the second driving control signal G2 and the first driving control signal G1 and the phase difference between the third driving control signal G3 and the second driving control signal G2, is the quotient of the reference switching cycle divided by the number n, and the phase adjustment is terminated.

[0128] S57: each driving control signal after phase adjustment is sent to each switching sub-circuit to trigger each switching sub-circuit to change the switching state.

[0129] S57: each driving control signal after phase adjustment is sent to each switching sub-circuit to trigger each switching sub-circuit to change the switching state. Figure 1 S57: each driving control signal after phase adjustment is sent to each switching sub-circuit to trigger each switching sub-circuit to change the switching state.

[0130] Further, in an embodiment, the above S54 can be further replaced by multiplying the duty cycle of the driving control signal by a set multiple; or, multiplying the adjustment output parameter of the corresponding PI controller by a set multiple, so as to generate the driving control signal by using the adjusted adjustment output signal.

[0131] It can be understood that, in order to simultaneously consider the contradiction between the output current Io rising time and the overshoot, the output current Io rising process can be further modulated by gradually phase shifting the multi-phase parallel switching sub-circuit and changing the PI parameter, and in order to further avoid the vertical line of the overshoot, the duty cycle of the driving control signal or the adjustment output parameter of the PI controller or other arbitrary reasonable PI parameter can be reduced when the difference between the actual output current Io and the reference current is lower than a certain range, so as to achieve rapid desaturation and prevent the occurrence of overshoot, which is not limited in the present application.

[0132] The present application also provides an electronic device, please refer to Figure 11 , Figure 11 is a structural schematic diagram of an embodiment of the electronic device of the present application. In the embodiment, the electronic device 60 comprises a shell 61 and a third charge control circuit 62 connected to the shell 61.

[0133] It should be noted that the third charge control circuit 62 described in the embodiment is the first charge control circuit 20 or the second charge control circuit described in any of the above embodiments, and details are described with reference to the above description of the first charge control circuit 20 or the second charge control circuit. Figures 1-10 and related text content, which will not be repeated here.

[0134] The beneficial effects of the present application are: Different from the prior art, the charge control method provided by the present application acquires the pulse reference current and the power supply characteristic parameters of the multi-phase voltage conversion circuit, generates a set number of driving control signals by using the set number, the pulse reference current and the power supply characteristic parameters in response to the rising edge of the pulse reference current, and the first rising edge of each driving control signal is synchronized, so that each switch sub-circuit can be triggered to conduct simultaneously by using each driving control signal, the rising speed of the output current is effectively improved, the rising time of the output current is significantly reduced, and each driving control signal is phase-modulated by using the set number and the preset switching period, so that each switch sub-circuit is gradually staggered to conduct, which can also effectively avoid the overshoot problem that may occur, so that the faster rising time of the output current can be considered at the same time, and the occurrence of overshoot can be avoided.

[0135] The above is only an embodiment of the present application, and does not limit the patent scope of the present application, and any equivalent structure or equivalent flow transformation using the content of the specification and drawings, or direct or indirect application in other related technical fields, are also included in the patent protection scope of the present application.

Claims

1. A charge control method, applied to charge control of a multi-phase voltage conversion circuit, wherein the multi-phase voltage conversion circuit includes a set number of switch sub-circuits, the set number being greater than 1, characterized in that: The charge control method comprises: Acquire a pulse reference current and power supply characteristic parameters of the multi-phase voltage conversion circuit; wherein the power supply characteristic parameters include input voltage, output voltage, output current, equivalent inductance, and a preset adjustment coefficient; In response to the rising edge of the pulse reference current, the set number of drive control signals are generated using the set number, the pulse reference current and the power supply characteristic parameter; wherein the first rising edge of each of the drive control signals is synchronized, and the drive control signal includes a first control signal and a second control signal; the step of generating the set number of drive control signals using the pulse reference current and the power supply characteristic parameter in response to the rising edge of the pulse reference current comprises: in response to the rising edge of each pulse reference current, obtaining a reference turn-on time using the input voltage, the output voltage, the pulse reference current, the set number, the equivalent inductance and the preset adjustment coefficient; generating the set number of first control signals using the reference turn-on time; wherein the rising edge of each of the first control signals is synchronized; after generating the first control signal, generating the second control signal using the difference between the pulse reference current and the output current until the next rising edge of the pulse reference current; Phase-modulating each of the drive control signals using the set number and the preset switching period; Each of the phase-adjusted driving control signals is sent to each of the switch sub-circuits to trigger each of the switch sub-circuits to change their switch states.

2. The charge control method according to claim 1, wherein: The step of phase-modulating each of the driving control signals using the set number and the preset switching period includes: The phase difference between each two adjacent falling edges of the first control signals is adjusted to the quotient of the preset switching period divided by the set number, and the sum of the on-times of the first control signals is made equal to the product of the reference on-time and the set number.

3. The charge control method according to claim 2, wherein: The step of generating the second control signal by using the difference between the pulse reference current and the output current comprises: In response to each falling edge of the first control signal, the second control signal is generated by delaying the setting time length and utilizing the difference between the pulse reference current and the output current.

4. The charge control method according to claim 1, wherein: The step of obtaining the reference on-time by using the input voltage, the output voltage, the pulse reference current, the set number, the equivalent inductance, and the preset adjustment coefficient includes: The reference on-time is obtained by calculating the input voltage, the output voltage, the pulse reference current, the set number, the equivalent inductance, and the preset adjustment coefficient using a preset adjustment function; Wherein, the preset adjustment function is: tj= ; Wherein, tj is the reference opening time, is the pulse reference current, is the preset adjustment coefficient, n is the set number, is the input voltage, is the output voltage, is the equivalent inductance.

5. The charge control method according to claim 1, wherein: The power supply characteristic parameter further includes an input current, and the step of generating the second control signal by using the difference between the pulse reference current and the output current includes: Performing proportional-integral adjustment on the current difference between the pulse reference current and the output current to obtain a target current integral value; Performing energy storage integral regulation on the input current to obtain an integral voltage value; obtaining an integral reference value by using a difference between a given reference voltage and the integral voltage value; The second control signal is obtained using the target current integral value and the integral reference value.

6. The charge control method according to claim 1, wherein: The power supply characteristic parameter includes an output current, and the step of generating the set number of drive control signals using the pulse reference current and the power supply characteristic parameter includes: Performing proportional-integral adjustment on the current difference between the pulse reference current and the output current to obtain a target current integral value; The set number of driving control signals is obtained by using the target current integral value.

7. The charge control method according to claim 6, wherein: The step of obtaining the set number of drive control signals by using the target current integral value further includes: Detecting whether the current difference is less than a set current threshold; If the current difference is less than the set current threshold, multiply the target current integral value by a set multiple; wherein the set multiple is less than 1 and greater than 0; Alternatively, the duty cycle of the driving control signal is multiplied by the set multiple.

8. The charge control method according to claim 6, wherein: The step of phase-modulating each of the driving control signals using the set number and the preset switching period includes: In each switching cycle of the drive control signal, a preset positive correlation function is used to gradually adjust the phase difference between each two adjacent drive control signals until the phase difference between each two adjacent drive control signals is the quotient of the preset switching cycle divided by the set number.

9. A charge control circuit, characterized in that: The charge control circuit is coupled to the multi-phase voltage conversion circuit; The charge control circuit performs charge control on the multi-phase voltage conversion circuit using the charge control method according to any one of claims 1 to 8.

10. An electronic device, characterized in that: The electronic device includes a housing and a charge control circuit connected to the housing; Wherein, the charge regulation circuit is the charge control circuit as claimed in claim 9.

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