A transimpedance flip-flop voltage follower driven linear regulator

Abstract

This invention provides a transimpedance flip-flop voltage follower driven linear regulator, including a control module and a transimpedance flip-flop voltage follower (TIFVF) module. The control module includes a series-connected error amplifier and a voltage-to-current converter. The output voltage Vout is fed back to the error amplifier after passing through a selectable voltage divider resistor and compared with the reference voltage Vref to obtain an error signal. After amplification and conditioning by a compensation network, a control voltage signal Vctrl is obtained. After passing through a voltage-to-current conversion circuit, the current control signal Ictrl required by the TIFVF can be obtained. The whole system forms a negative feedback loop, in which the error amplifier and voltage-to-current conversion stages provide sufficient loop gain.

Description

Technical Field

[0001] This invention relates to the field of linear regulators, and more specifically, to a transimpedance flip-flop voltage follower driven linear regulator. Background Technology

[0002] As a crucial interface connecting signal processing units and power devices, the performance of the driver circuit directly impacts the efficiency and stability of the entire electronic system. A review of the development history of driver circuits clearly shows the technological evolution from traditional source followers to flip-flop voltage followers (FVF) circuits. Early driver circuits primarily employed simple source follower structures, resulting in high output impedance that failed to meet the driving capability requirements of modern electronic devices. With technological advancements, researchers proposed FVF circuits based on the principle of negative feedback. Through local negative feedback structures, the output resistance is reduced by several to tens of times, significantly improving the circuit's driving performance.

[0003] The development of low-dropout linear regulator (LDO) technology has provided an important platform for the application of flip-flop (FVF) circuits. Traditional LDO circuits employ a voltage divider composed of upper and lower resistors connected in parallel with a compensation capacitor. While this provides a leading zero, when the resistance ratio is small, the zero and poles are quite close, significantly reducing the phase compensation effect. To address this issue, the academic community has proposed various improvements, including transconductance gain enhancement architectures and techniques using voltage-controlled current sources for compensation. These technological advancements laid the theoretical foundation for the emergence of FVF voltage-flipping driver stage circuits.

[0004] In recent years, with the widespread adoption of SoC chips, the demand for high-performance LDO circuits has increased dramatically. FVF-type LDOs, with FVF control modules at their core, have attracted considerable attention due to their superior performance in low power consumption, high load current, high power supply rejection ratio, and transient response.

[0005] FVF-type LDOs have become widely popular in recent years, and the core of FVF is as follows: Figure 1 As shown, the external control module adjusts V CTRL The voltage controls the output voltage Vout. The FVF structure achieves a fast response to changes in load current through a local feedback loop Mp1-Mn1-Mpower.

[0006] However, compared to traditional LDO structures, FVFs have larger DC errors and poorer load regulation, requiring additional compensation for high loop gain to suppress them. Furthermore, their power supply rejection ratio is also worse than traditional LDOs, and their output voltage swing is limited by the Vgs value of the Mp1 transistor. On the other hand, the primary function of FVFs and traditional LDOs is to provide current to the external circuitry. Figure 1The medium-power transistor Mpower uses PMOS to achieve this function, but PMOS is naturally slower to respond to load changes than NMOS. Even though the local loop of FVF improves this problem, the active loop is always limited by bandwidth and slew rate. For applications with large load currents, such as greater than 1A, the required chip area and power consumption will increase dramatically.

[0007] Therefore, how to balance fast response, high-precision voltage regulation, wide adjustment range and good anti-interference capability under high load current conditions has become the core challenge in the design of linear regulators. Summary of the Invention

[0008] The purpose of this invention is to address the problems of large DC error, poor load regulation, and the need for additional compensation of high loop gain in traditional LDO structures for suppression. It proposes a transimpedance flip-flop voltage follower driven linear regulator that can quickly respond to large load current jumps, while having high DC accuracy, load regulation, and high power supply rejection ratio, as well as a wider output voltage range.

[0009] The technical solution of this invention is:

[0010] This invention provides a transimpedance flip-flop voltage follower driven linear regulator, comprising a control module and a transimpedance flip-flop voltage follower (TIFVF) module, wherein;

[0011] The control module includes an error amplifier and a voltage-to-current converter connected in series. The inverting terminal of the error amplifier is connected to the output terminal Vout of the TIFVF module. A compensation network is provided between the error amplifier and the voltage-to-current converter. The voltage-to-current converter outputs a current signal Ictrl as a control signal and connects it to the control signal input terminal of the TIFVF module.

[0012] The control signal input terminal of the TIFVF module is connected to the current control signal Ictrl output by the voltage-to-current converter; the power supply terminal of the TIFVF module is connected to the input voltage Vin, which can be an independent input source or connected to the power supply VDD; the output terminal of the TIFVF module is connected to the load and also serves as a feedback signal connected to the inverting input of the error amplifier in the control module.

[0013] The inverting input of the error amplifier acquires the output voltage Vout of the TIFVF module and compares it with the reference voltage Vref at the non-inverting input to generate an error signal. The error signal is then amplified and processed by a compensation network to generate a control voltage signal Vctrl. The control voltage signal Vctrl is then converted into a current control signal Ictrl by a voltage-to-current converter. The current control signal Ictrl is input to the TIFVF module to adjust the output voltage Vout, forming a negative feedback loop.

[0014] Furthermore, the TIFVF module includes:

[0015] A DC bias circuit includes an equivalent resistor Req, transistors Mp1 and Mp2, and current sources Ibias1 and Ibias2. The source of transistor Mp2 is connected to the current control signal Ictrl and the power supply VDD, the drain is connected to the current source Ibias1 in series and then grounded, and the gate is connected to the gate of transistor Mp1. The drain of transistor Mp1 is connected to the current source Ibias2 in series and then grounded. One end of the equivalent resistor Req is connected to the source of transistor Mp2, and the other end is connected to the output terminal Vout.

[0016] The TIFVF receives the current control signal Ictrl as input, and performs DC operating point bias through a DC bias circuit to decouple the bias relationship between the control voltage signal Vctrl and the output voltage Vout established by transistor Mn1.

[0017] The local negative feedback loop includes transistors Mp1, Mn1, Mp3 and capacitor C. The source of transistor Mp3 is connected to power supply VDD, and the drain is connected to the source of transistor Mp1. The connection point of transistors Mp3 and Mp1 is connected to the gate of power transistor Mpower. The source of power transistor Mpower serves as the output terminal Vout, and the drain is connected to the input voltage Vin. The connection point of the gate and source of transistor Mp3 is connected to one end of capacitor C, and the other end of capacitor C is connected to power supply VDD. The two ends of capacitor C are connected in parallel to current source Ibias1, and the output of current source Ibias1 is connected to the drain of transistor Mn1. The source of transistor Mn1 is connected in series with current source Ibias2 and then grounded.

[0018] The negative feedback loop forms a local negative feedback through transistors Mp1, Mn1 and Mp3, which reduces the equivalent resistance of the gate node of the power transistor Mpower.

[0019] The TIFVF module generates an output voltage Vout based on the current control signal Ictrl, and the output voltage Vout ranges from ground potential to input voltage Vin; it pushes the pole of the gate node of the power transistor Mpower to a high frequency, improving the response speed and power supply rejection ratio.

[0020] Furthermore, the DC bias circuit performs the following steps:

[0021] A reference voltage is established through the equivalent resistance Req to stabilize the operating state of transistor Mp2;

[0022] The static operating current of transistor Mp2 is provided by current source Ibias1 to determine the conduction threshold of transistor Mp2; the static operating current of transistor Mp1 is provided by current source Ibias2.

[0023] Establish a current mirror relationship between transistors Mp1 and Mp2 to eliminate the direct influence of the control voltage signal Vctrl on the output voltage Vout.

[0024] Furthermore, the local negative feedback loop performs the following steps:

[0025] The gate of transistor Mp1 is used as the input stage to receive the voltage signal obtained by the current control signal Ictrl through transistor Mp2. After passing through the local negative feedback loop formed by transistors Mp1-Mn1-Mp3, the source of transistor Mp1 will follow the change of the source of transistor Mp2.

[0026] For this local negative feedback loop, the source of transistor Mp1 is used as the loop input stage. The voltage signal is converted into a current signal after passing through transistor Mp1, and then through the drain of transistor Mp1 and the source of transistor Mn1. The voltage signal is amplified by the small-signal equivalent resistance of the drain node of transistor Mn1 and transmitted to the gate of transistor Mp3. It is then converted into a current by transistor Mp3 and flows out from the drain of transistor Mp3. The voltage signal is converted back into a voltage signal by the small-signal equivalent resistance of the drain node, which is the output stage of this local negative feedback loop.

[0027] After the local negative feedback loop is closed, the impedance transformation effect of the negative feedback loop will reduce the small-signal equivalent resistance of the gate node of the power transistor Mpower, so that the low-frequency pole will shift to the high-frequency band.

[0028] Furthermore, transistors Mp1, Mp2, and Mp3 are PMOS transistors, while transistor Mn1 and power transistor Mpower are NMOS transistors; or transistors Mp1, Mp2, and Mp3 are NMOS transistors, while transistor Mn1 and power transistor Mpower are PMOS transistors.

[0029] Furthermore, a voltage divider circuit is provided between the inverting terminal of the error amplifier and the output terminal Vout of the TIFVF module; the voltage divider circuit includes two series resistors, one end of which is connected to the output terminal Vout and the other end is grounded. The connection point of the series resistors serves as the output of the voltage divider circuit, generating a feedback voltage Vfb which is output to the inverting input terminal of the error amplifier.

[0030] Furthermore, in the voltage divider circuit, a capacitor is connected in parallel with the upper resistor to improve the power supply rejection ratio.

[0031] Furthermore, the compensation network includes a series RC branch or a parallel RC branch, one end of which is connected to the control voltage signal Vctrl, and the other end is grounded.

[0032] Furthermore, the load is equivalent to a parallel circuit of a capacitor and a resistive load, or a parallel circuit of a capacitor and a constant current source load.

[0033] Furthermore, the error amplifier is composed of a transconductance amplifier OTA or an operational amplifier OPA.

[0034] The beneficial effects of this invention are:

[0035] This invention discloses a linear regulator suitable for high load current applications. It adopts a transimpedance flip-flop voltage follower structure and improves the response speed through NMOS transistors and local negative feedback loops. It introduces a control current signal as input to decouple the limiting relationship between the output voltage and the control voltage, thereby achieving a wide output voltage range. By configuring an equivalent resistance and a bias current source, it stabilizes the DC operating point and ensures that the output voltage covers the entire range.

[0036] This invention constructs an overall negative feedback loop through an error amplifier and a feedback network, improves the power supply rejection ratio through a voltage divider resistor device and a parallel capacitor, and optimizes the loop stability and transient response through a compensation network.

[0037] This invention achieves fast response, high DC accuracy, and wide output voltage range under high load current through innovative structural design and control methods, effectively solving the performance bottleneck problem of traditional linear regulators in such applications.

[0038] Other features and advantages of the present invention will be described in detail in the following detailed description section. Attached Figure Description

[0039] The above and other objects, features and advantages of the present invention will become more apparent from the more detailed description of exemplary embodiments of the invention in conjunction with the accompanying drawings, wherein the same reference numerals generally represent the same components in the exemplary embodiments of the invention.

[0040] Figure 1 A schematic diagram of the core circuit of the FVF module in the background art is shown.

[0041] Figure 2 A system architecture diagram of the transimpedance flip-flop voltage follower driven linear regulator of the present invention is shown.

[0042] Figure 3 The circuit diagram of the TIFVF module in this invention is shown.

[0043] Figure 4 The voltage divider circuit diagram of this invention is shown.

[0044] Figure 5 The circuit diagram of the compensation network in this invention is shown.

[0045] Figure 6 The load circuit diagram of this invention is shown.

[0046] Figure 7 The circuit diagram of the error amplifier in this invention is shown.

[0047] Figure 8 The circuit diagram of the voltage-current converter in this invention is shown. Detailed Implementation

[0048] Preferred embodiments of the invention will now be described in more detail with reference to the accompanying drawings. While preferred embodiments of the invention are shown in the drawings, it should be understood that the invention can be implemented in various forms and should not be limited to the embodiments set forth herein.

[0049] Figure 2 A system architecture diagram of the transimpedance flip-flop voltage follower driven linear regulator of the present invention is shown.

[0050] like Figure 2 As shown, the present invention provides a transimpedance flip-flop voltage follower driven linear regulator, including a control module and a transimpedance flip-flop voltage follower (TIFVF) module, wherein;

[0051] The control module includes an error amplifier and a voltage-to-current converter connected in series. The inverting terminal of the error amplifier is connected to the output terminal Vout of the TIFVF module. A compensation network is provided between the error amplifier and the voltage-to-current converter. The voltage-to-current converter outputs a current signal Ictrl as a control signal and connects it to the control signal input terminal of the TIFVF module.

[0052] The control signal input terminal of the TIFVF module is connected to the current control signal Ictrl output by the voltage-to-current converter; the power supply terminal of the TIFVF module is connected to the input voltage Vin, which can be an independent input source or connected to the power supply VDD; the output terminal of the TIFVF module is connected to the load and also serves as a feedback signal connected to the inverting input of the error amplifier in the control module.

[0053] The inverting input of the error amplifier acquires the output voltage Vout of the TIFVF module and compares it with the reference voltage Vref at the non-inverting input to generate an error signal. The error signal is then amplified and processed by a compensation network to generate a control voltage signal Vctrl. The control voltage signal Vctrl is then converted into a current control signal Ictrl by a voltage-to-current converter. The current control signal Ictrl is input to the TIFVF module to adjust the output voltage Vout, forming a negative feedback loop.

[0054] In this embodiment, the output voltage VOUT is fed back to the error amplifier and compared with the reference voltage VREF to obtain the error signal. After amplification and conditioning by the compensation network, the control voltage signal VCTRL is obtained. VCTRL is then passed through a voltage-to-current conversion circuit to obtain the current control signal ICTRL required by TIFVF. The whole circuit forms a negative feedback loop, in which the error amplifier and voltage-to-current conversion stages provide sufficient loop gain.

[0055] like Figure 3 As shown, the TIFVF module includes:

[0056] A DC bias circuit includes an equivalent resistor Req, transistors Mp1 and Mp2, and current sources Ibias1 and Ibias2. The source of transistor Mp2 is connected to the current control signal Ictrl and the power supply VDD, the drain is connected to the current source Ibias1 in series and then grounded, and the gate is connected to the gate of transistor Mp1. The drain of transistor Mp1 is connected to the current source Ibias2 in series and then grounded. One end of the equivalent resistor Req is connected to the source of transistor Mp2, and the other end is connected to the output terminal Vout.

[0057] The TIFVF receives the current control signal Ictrl as input, and performs DC operating point bias through a DC bias circuit to decouple the bias relationship between the control voltage signal Vctrl and the output voltage Vout established by transistor Mn1.

[0058] The local negative feedback loop includes transistors Mp1, Mn1, Mp3 and capacitor C. The source of transistor Mp3 is connected to power supply VDD, and the drain is connected to the source of transistor Mp1. The connection point of transistors Mp3 and Mp1 is connected to the gate of power transistor Mpower. The source of power transistor Mpower serves as the output terminal Vout, and the drain is connected to the input voltage Vin. The connection point of the gate and source of transistor Mp3 is connected to one end of capacitor C, and the other end of capacitor C is connected to power supply VDD. The two ends of capacitor C are connected in parallel to current source Ibias1, and the output of current source Ibias1 is connected to the drain of transistor Mn1. The source of transistor Mn1 is connected in series with current source Ibias2 and then grounded.

[0059] The negative feedback loop forms a local negative feedback through transistors Mp1, Mn1 and Mp3, which reduces the equivalent resistance of the gate node of the power transistor Mpower.

[0060] The TIFVF module generates an output voltage Vout based on the current control signal Ictrl, and the output voltage Vout ranges from ground potential to input voltage Vin; it pushes the pole of the gate node of the power transistor Mpower to a high frequency, improving the response speed and power supply rejection ratio.

[0061] In one example, the DC bias circuit performs the following steps:

[0062] A reference voltage is established through the equivalent resistance Req to stabilize the operating state of transistor Mp2;

[0063] The static operating current of transistor Mp2 is provided by current source Ibias1 to determine the conduction threshold of transistor Mp2; the static operating current of transistor Mp1 is provided by current source Ibias2.

[0064] Establish a current mirror relationship between transistors Mp1 and Mp2 to eliminate the direct influence of the control voltage signal Vctrl on the output voltage Vout.

[0065] In this embodiment, a control current signal is introduced as input from the transimpedance flip-flop voltage follower structure. This control current signal is generated by a voltage-to-current conversion circuit and works in conjunction with a DC bias circuit to decouple the limiting relationship between the output voltage and the control voltage. An equivalent resistance and a bias current source are configured for the control current signal. This configuration is used to stabilize the DC operating point, ensuring that the output voltage range covers the entire range from ground voltage to the input voltage. The DC operating point bias prevents the output voltage Vout from being affected by... Figure 1 Gate-source voltage limitation of transistor Mp1.

[0066] In one example, a local negative feedback loop performs the following steps:

[0067] The gate of transistor Mp1 is used as the input stage to receive the voltage signal obtained by the current control signal Ictrl through transistor Mp2. After passing through the local negative feedback loop formed by transistors Mp1-Mn1-Mp3, the source of transistor Mp1 will follow the change of the source of transistor Mp2.

[0068] For this local negative feedback loop, the source of transistor Mp1 is used as the loop input stage. The voltage signal is converted into a current signal after passing through transistor Mp1, and then through the drain of transistor Mp1 and the source of transistor Mn1. The voltage signal is amplified by the small-signal equivalent resistance of the drain node of transistor Mn1 and transmitted to the gate of transistor Mp3. It is then converted into a current by transistor Mp3 and flows out from the drain of transistor Mp3. The voltage signal is converted back into a voltage signal by the small-signal equivalent resistance of the drain node, which is the output stage of this local negative feedback loop.

[0069] After the local negative feedback loop is closed, the impedance transformation effect of the negative feedback loop will reduce the small-signal equivalent resistance of the gate node of the power transistor Mpower, so that the low-frequency pole will shift to the high-frequency band.

[0070] In this embodiment, a local negative feedback loop is constructed using a loop structure composed of multiple transistors; the equivalent resistance of the output node is reduced through the local negative feedback loop; the stability of the output voltage is adjusted according to the feedback characteristics of the local negative feedback loop, enabling a rapid response to changes in load current; and the configuration of the local negative feedback loop optimizes the DC accuracy of the circuit and improves the overall load regulation of the circuit.

[0071] In this invention, transistors Mp1, Mp2, and Mp3 are PMOS transistors; transistors Mn1 and Mpower are NMOS transistors; or transistors Mp1, Mp2, and Mp3 are NMOS transistors; and transistors Mn1 and Mpower are PMOS transistors.

[0072] In one example, such as Figure 4 The diagram shows a voltage divider circuit in this invention. A voltage divider circuit is provided between the inverting terminal of the error amplifier and the output terminal Vout of the TIFVF module. The voltage divider circuit includes two series resistors. One end of the series resistor is connected to the output terminal Vout, and the other end is grounded. The connection point of the series resistor serves as the output of the voltage divider circuit, generating a feedback voltage Vfb which is output to the inverting input terminal of the error amplifier. In the voltage divider circuit, a capacitor is connected in parallel with the upper resistor to improve the power supply rejection ratio.

[0073] In this embodiment, the voltage divider circuit divides the output voltage to generate a feedback voltage, and improves the power supply rejection ratio through a parallel capacitor.

[0074] In one example, such as Figure 5 The circuit diagram of the compensation network in this invention is shown; the compensation network includes series RC branches or parallel RC branches, one end of the series RC branch or parallel RC branch is connected to the control voltage signal Vctrl, and the other end is grounded.

[0075] In this embodiment, the parameters of the compensation network are adjusted according to the output characteristics of the transimpedance flip-flop voltage follower structure. The compensation network is composed of a combination of resistors and capacitors and is used to optimize loop stability and transient response.

[0076] In one example Figure 6 The diagram shows a load circuit in this invention, where the load is equivalent to a parallel circuit of a capacitor and a resistive load, or a parallel circuit of a capacitor and a constant current source load.

[0077] In this embodiment, an equivalent circuit including capacitive and resistive loads is constructed for the load model of the linear regulator to simulate actual load switching scenarios and verify the dynamic response performance of the regulator.

[0078] In one example Figure 7The circuit diagram of the error amplifier in this invention is shown. The error amplifier is composed of a transconductance amplifier OTA or an operational amplifier OPA.

[0079] The various embodiments of the present invention have been described above. These descriptions are exemplary and not exhaustive, nor are they limited to the disclosed embodiments. Many modifications and variations will be apparent to those skilled in the art without departing from the scope and spirit of the described embodiments.

Claims

1. A transimpedance flip-flop voltage follower driven linear regulator, characterized in that... This includes a control module and a transimpedance flip-flop voltage follower (TIFVF) module, wherein; The control module includes an error amplifier and a voltage-to-current converter connected in series. The inverting terminal of the error amplifier is connected to the output terminal Vout of the TIFVF module. A compensation network is provided between the error amplifier and the voltage-to-current converter. The voltage-to-current converter outputs a current signal Ictrl as a control signal and connects it to the control signal input terminal of the TIFVF module. The control signal input terminal of the TIFVF module is connected to the current control signal Ictrl output by the voltage-to-current converter; the power supply terminal of the TIFVF module is connected to the input voltage Vin, which can be an independent input source or connected to the power supply VDD; the output terminal of the TIFVF module is connected to the load and also serves as a feedback signal connected to the inverting input of the error amplifier in the control module. The inverting input of the error amplifier acquires the output voltage Vout of the TIFVF module and compares it with the reference voltage Vref at the non-inverting input to generate an error signal. The error signal is then amplified and processed by a compensation network to generate a control voltage signal Vctrl. The control voltage signal Vctrl is then converted into a current control signal Ictrl by a voltage-to-current converter. The current control signal Ictrl is input to the TIFVF module to adjust the output voltage Vout, forming a negative feedback loop. The TIFVF module includes: A DC bias circuit includes an equivalent resistor Req, transistors Mp1 and Mp2, and current sources Ibias1 and Ibias2. The source of transistor Mp2 is connected to the current control signal Ictrl and the power supply VDD, the drain is connected to the current source Ibias1 in series and then grounded, and the gate is connected to the gate of transistor Mp1. The drain of transistor Mp1 is connected to the current source Ibias2 in series and then grounded. One end of the equivalent resistor Req is connected to the source of transistor Mp2, and the other end is connected to the output terminal Vout. The TIFVF receives the current control signal Ictrl as input, and performs DC operating point bias through a DC bias circuit to decouple the bias relationship between the control voltage signal Vctrl and the output voltage Vout established by transistor Mn1. The local negative feedback loop includes transistors Mp1, Mn1, Mp3 and capacitor C. The source of transistor Mp3 is connected to power supply VDD, and the drain is connected to the source of transistor Mp1. The connection point of transistors Mp3 and Mp1 is connected to the gate of power transistor Mpower. The source of power transistor Mpower serves as the output terminal Vout, and the drain is connected to the input voltage Vin. The connection point of the gate and source of transistor Mp3 is connected to one end of capacitor C, and the other end of capacitor C is connected to power supply VDD. The two ends of capacitor C are connected in parallel to current source Ibias1, and the output of current source Ibias1 is connected to the drain of transistor Mn1. The source of transistor Mn1 is connected in series with current source Ibias2 and then grounded. The negative feedback loop forms a local negative feedback through transistors Mp1, Mn1 and Mp3, which reduces the equivalent resistance of the gate node of the power transistor Mpower. The TIFVF module generates an output voltage Vout based on the current control signal Ictrl, and the output voltage Vout ranges from ground potential to input voltage Vin; it pushes the pole of the gate node of the power transistor Mpower to a high frequency, improving the response speed and power supply rejection ratio.

2. The transimpedance reversing voltage follower driven linear regulator according to claim 1, characterized in that... The DC bias circuit performs the following steps: A reference voltage is established through the equivalent resistance Req to stabilize the operating state of transistor Mp2; The static operating current of transistor Mp2 is provided by current source Ibias1 to determine the conduction threshold of transistor Mp2; the static operating current of transistor Mp1 is provided by current source Ibias2. Establish a current mirror relationship between transistors Mp1 and Mp2 to eliminate the direct influence of the control voltage signal Vctrl on the output voltage Vout.

3. The transimpedance flip-flop voltage follower driven linear regulator according to claim 1, characterized in that... The local negative feedback loop performs the following steps: The gate of transistor Mp1 is used as the input stage to receive the voltage signal obtained by the current control signal Ictrl through transistor Mp2. After passing through the local negative feedback loop formed by transistors Mp1-Mn1-Mp3, the source of transistor Mp1 will follow the change of the source of transistor Mp2. For this local negative feedback loop, the source of transistor Mp1 is used as the loop input stage. The voltage signal is converted into a current signal after passing through transistor Mp1, and then through the drain of transistor Mp1 and the source of transistor Mn1. The voltage signal is amplified by the small-signal equivalent resistance of the drain node of transistor Mn1 and transmitted to the gate of transistor Mp3. It is then converted into a current by transistor Mp3 and flows out from the drain of transistor Mp3. The voltage signal is converted back into a voltage signal by the small-signal equivalent resistance of the drain node, which is the output stage of this local negative feedback loop. After the local negative feedback loop is closed, the impedance transformation effect of the negative feedback loop will reduce the small-signal equivalent resistance of the gate node of the power transistor Mpower, so that the low-frequency pole will shift to the high-frequency band.

4. The transimpedance flip-flop voltage follower driven linear regulator according to claim 1, characterized in that... The transistors Mp1, Mp2, and Mp3 are PMOS transistors, while transistor Mn1 and power transistor Mpower are NMOS transistors; or transistors Mp1, Mp2, and Mp3 are NMOS transistors, while transistor Mn1 and power transistor Mpower are PMOS transistors.

5. The transimpedance flip-flop voltage follower driven linear regulator according to claim 1, characterized in that... A voltage divider circuit is provided between the inverting terminal of the error amplifier and the output terminal Vout of the TIFVF module. The voltage divider circuit includes two series resistors. One end of the series resistor is connected to the output terminal Vout, and the other end is grounded. The connection point of the series resistor serves as the output of the voltage divider circuit, generating a feedback voltage Vfb which is output to the inverting input terminal of the error amplifier.

6. The transimpedance flip-flop voltage follower driven linear regulator according to claim 5, characterized in that... In the voltage divider circuit, a capacitor is connected in parallel with the upper resistor to improve the power supply rejection ratio.

7. The transimpedance flip-flop voltage follower driven linear regulator according to claim 1, characterized in that... The compensation network includes a series RC branch or a parallel RC branch, with one end of the series RC branch or the parallel RC branch connected to the control voltage signal Vctrl and the other end grounded.

8. The transimpedance flip-flop voltage follower driven linear regulator according to claim 1, characterized in that... The load is equivalent to a parallel circuit of a capacitor and a resistive load, or a parallel circuit of a capacitor and a constant current source load.

9. The transimpedance flip-flop voltage follower driven linear regulator according to claim 1, characterized in that... The error amplifier is composed of a transconductance amplifier OTA or an operational amplifier OPA.

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