Self-adaptive MPPT vibration energy collection and management chip based on charge transfer

Abstract

The invention provides a self-adaptive MPPT vibration energy collection and management chip based on charge transfer, and belongs to the technical field of vibration micro energy collection. According to the invention, the nine-phase SSHC module controls the total series resistance value of the flip capacitor during the charge transfer period; the full-wave bridge active rectification module converts alternating current input into direct current output. The active diode collects the output of the full-wave bridge active rectifier module; the under-voltage locking module monitors an input voltage threshold value and controls a subsequent part to sleep or start working; the self-adaptive charge transfer MPPT algorithm module judges and calculates the maximum power point voltage at the moment according to the amplitude change of an input source, and carries out self-adaptive sampling and control on the maximum power point voltage. The vibration energy collecting device has high voltage overturning efficiency, internal logic abnormity or ineffective work at low voltage can be avoided, the adaptive maximum power point can be automatically and rapidly adjusted according to changes of the external environment, and the vibration energy collecting device is suitable for various vibration energy collecting scenes with different characteristics.

Description

Technical Field

[0001] The present invention relates to a charge transfer-based adaptive MPPT vibration energy collection and management chip, belonging to the technical field of vibration micro-energy collection. Background Art

[0002] As fundamental components of the Internet of Things (IoT), wireless sensor network nodes facilitate interaction between humans and the environment. To facilitate ease of use and reduce costs, they require high integration, low cost, compact size, long lifespan, and minimal maintenance. Therefore, battery-free, self-powered solutions offer an alternative to traditional mains-powered wireless networks. Self-powered sensor nodes incorporate energy harvesting modules that capture energy from the surrounding environment. These modules, through a power management module, convert this energy into electrical energy for use by other modules. These nodes are self-sufficient, independent of external power supplies, making energy independence a reality for sensor nodes and IoT devices.

[0003] Among various environmental alternative energy sources, vibration energy has attracted significant attention due to its diverse forms and excellent power density. As a popular alternative to batteries, vibration energy harvesters, particularly used as power supply modules in low-power wearable devices and wireless sensor networks, offer long-term stable operation and significantly reduce maintenance costs. While most energy harvesting circuits are similar to traditional power converters, the circuit designs used for vibration energy harvesting differ significantly from traditional circuits. For example, the energy source is not a fixed voltage or current source, but rather a load or environmental variable. The input energy is limited, and the input voltage amplitude can be very low or vary over a wide range. The operating voltage of the harvesting circuit must be defined at the maximum power point, otherwise the overall power conversion efficiency of the circuit may be reduced. Given the inherent characteristics of vibration energy harvesters and the power supply requirements of wireless sensor nodes, it is of great significance to promote the development and application of self-powered vibration energy harvesting technology that combines high efficiency and high stability.

[0004] Because the output voltage of a vibration energy harvester is an AC signal, an AC-DC converter is required to rectify the signal and obtain a DC output. The output energy is then stored in a supercapacitor or regulated by other power management modules to power the load. Traditional passive rectifiers, consisting of diodes, do not require additional control. However, under low-power conditions, the AC input voltage may not meet the diode's required turn-on voltage. Even if the input voltage reaches the turn-on voltage, the diode's required turn-on voltage significantly reduces the overall circuit conversion efficiency. Conjugate matching between the vibration energy harvester and the load circuit can optimize the energy harvester's conversion efficiency. However, most solutions require the addition of an off-chip inductor to synchronize the output voltage and current waveforms. While this can increase conversion efficiency within a certain range of excitation levels, it is difficult to integrate the design, and the inductor increases the required off-chip area. Therefore, high-efficiency rectifiers (SSHCs) without an off-chip inductor are of great research significance for implantable devices and miniaturized sensor nodes.

[0005] Since the vibration energy harvester has a low input amplitude of the ambient source, the circuit may work abnormally when the voltage is too low, resulting in invalid power consumption, or directly trigger a chain failure and cause damage. Therefore, when the input is undervoltage or fluctuates greatly, the energy harvester needs to be shut down and paused in time. After the input voltage exceeds the minimum threshold, the vibration energy harvester restarts to ensure the stability and reliability of the vibration energy harvesting chip.

[0006] Since the impedance of the vibration energy harvester near the resonant frequency is mainly resistive, under stable environmental conditions, each input condition will have a corresponding output voltage and current value, thereby generating maximum output power. Therefore, dynamic resistance matching can be achieved through MPPT (Maximum Power Point Tracking), thereby achieving efficient energy collection and significantly improving energy conversion efficiency. The traditional open-circuit voltage MPPT algorithm pre-sets a proportional coefficient based on the theoretical relationship between the maximum power point voltage VMPP and the open-circuit voltage VOC to directly control the voltage value. Although the circuit structure is simple, if the external vibration energy deviates from the preset conditions, it cannot automatically update the VOC corresponding to the current input. The tracking accuracy of VMPP is low, which directly leads to a decrease in efficiency and is not suitable for environments with large fluctuations in vibration amplitude. Therefore, the algorithm solution of dynamically tracking the maximum power point of the circuit has a wide range of application scenarios. It can adaptively adjust and track VMPP according to changes in the external environment, has a fast response speed, and reduces energy loss during the operation of the vibration energy harvesting chip.

[0007] To address this, this patent proposes an adaptive MPPT vibration energy harvesting and management chip based on charge transfer. Compared with other vibration energy harvesting and management circuits, it can not only complete the on-chip integrated AC-DC function and effectively improve the voltage reversal efficiency, but also has an undervoltage lockout protection mode. When the input is too low, it forces other modules to shut down to prevent the internal logic of the chip from increasing power consumption. At the same time, the adaptive MPPT algorithm scheme based on charge transfer can automatically adjust the maximum power point tracked inside the chip according to changes in the external vibration environment, and use the principle of capacitive charge transfer for voltage division. The response speed is significantly better than the resistive voltage division method, effectively improving tracking accuracy and reducing power consumption. This vibration energy harvesting and management chip has no external inductor, which is conducive to the high integration of the chip. It has excellent characteristics such as small area, low manufacturing cost and low energy loss. Summary of the Invention

[0008] The purpose of the present invention is to solve the problems existing in the above-mentioned prior art and to provide an adaptive MPPT vibration energy collection and management chip based on charge transfer.

[0009] The purpose of the present invention is achieved through the following technical solutions:

[0010] An adaptive MPPT vibration energy harvesting and management chip based on charge transfer, comprising: a nine-phase SSHC module, a full-wave bridge active rectifier module, an active diode, an undervoltage lockout module, and an adaptive charge transfer MPPT algorithm module;

[0011] The signal output end of the vibration energy input source equivalent model is respectively connected to the signal input end of the nine-phase SSHC module and the signal input end of the full-wave bridge active rectifier module. The signal output end of the nine-phase SSHC module is connected to the signal input end of the full-wave bridge active rectifier module. The signal output end of the full-wave bridge active rectifier module is respectively connected to the signal input end of the active diode and the signal input end of the adaptive charge transfer MPPT algorithm module. The signal output end of the active diode is respectively connected to the signal input end of the nine-phase SSHC module, the signal input end of the undervoltage lockout module and the signal input end of the adaptive charge transfer MPPT algorithm module. The signal output end of the undervoltage lockout module is connected to the signal input end of the adaptive charge transfer MPPT algorithm module. The signal output ends of the active diode, the undervoltage lockout module and the adaptive charge transfer MPPT algorithm module are all connected to the signal input end of the battery management system.

[0012] Preferably, the nine-phase SSHC module is used to control the total series resistance value of the capacitance of the equivalent model of the vibration energy input source and the flip capacitor in the nine-phase SSHC module during the charge transfer period;

[0013] Full-wave bridge active rectifier module, used to convert AC input signal into DC output signal;

[0014] Active diodes for processing the output signal of the energy harvesting full-wave bridge active rectifier module;

[0015] Undervoltage lockout module, used to monitor the input voltage threshold and control the adaptive charge transfer MPPT algorithm module and battery management system to sleep or start working;

[0016] The adaptive charge transfer MPPT algorithm module is used to determine and calculate the corresponding maximum power point voltage when the input current amplitude of the equivalent model of the vibration energy input source changes, and adaptively sample and control the maximum power point voltage. The calculation formula of the maximum power point voltage obtained by sampling is as follows:

[0017] V MPPT =(2C PEH (V B / 2+V OC )) / (C PEH +C MPPT )

[0018] Among them, V MPPT C is the voltage value obtained by the sampling circuit in the adaptive charge transfer MPPT algorithm module after sampling and voltage division. PEH is the parasitic capacitance value in the equivalent model of the vibration energy input source, V B The input voltage value provided by the equivalent model of the vibration energy input source after the voltage reversal of one cycle is completed, V OC is the output voltage of the full-wave bridge active rectifier module when the active diode is open circuit, C MPPT is the sampling circuit value of the sampling circuit in the adaptive charge transfer MPPT algorithm module;

[0019] The battery management system is used to further control the output of the active diode, undervoltage lockout module and adaptive charge transfer MPPT algorithm module to ultimately power the load.

[0020] Preferably, the nine-phase SSHC module includes: eleven transmission gate switches, three flip capacitors and a switch logic clock circuit; the eleven transmission gate switches are two switches SW P , two switches SW N , switch SW1, switch SW2, switch SW3, two switches SW4 and two switches SW5; the three flip capacitors are flip capacitor C2, flip capacitor C3 and flip capacitor C4;

[0021] The signal output end of the switch logic clock circuit is connected to each transmission gate switch; the two switches SW P With the two switches SW NAfter one-to-one correspondence and series connection, branches are obtained respectively. The two switches SW4 and the two switches SW5 are connected in series one-to-one to obtain branches respectively. The four branches are connected in parallel. The upper plate of the flip capacitor C2 is connected to the switch SW P With switch SW N In one of the series branches, the lower plate of the flip capacitor C2 is connected to one end of the switch SW1, the other end of the switch SW1 is connected to the upper plate of the flip capacitor C3, and the lower plate of the flip capacitor C3 is connected to the switch SW P With switch SW N Another branch in series; one end of the switch SW2 is connected between the switch SW1 and the flip capacitor C2, and the other end is connected to the lower plate of the flip capacitor C3; one end of the switch SW3 is connected to the upper plate of the flip capacitor C2, and the other end is connected between the switch SW1 and the flip capacitor C2; the upper plate of the flip capacitor C4 is connected to one of the branches connected in series with the branch switches SW4 and SW5, and the lower plate of the flip capacitor C4 is connected to the other branch connected in series with the branch switches SW4 and SW5;

[0022] A transmission gate switch for controlling the total series resistance of the flip capacitor during charge transfer;

[0023] Flip capacitor, used to store and transfer charge;

[0024] The switching logic clock circuit is used to provide control signals for the transmission gate switches.

[0025] Preferably, the full-wave bridge active rectifier module includes: two comparators, two NMOS switches, and two cross-coupled PMOS switches; the two comparators are respectively Comparator 1 COMP1 and Comparator 2 COMP1; the two NMOS switches are respectively switch NM1 and switch NM2; the two cross-coupled PMOS switches are respectively switch PM1 and switch PM2;

[0026] The gate of switch NM1 is connected to the output terminal of comparator 1 COMP1, the gate of switch NM2 is connected to the output terminal of comparator 2 COMP1, the drain of switch PM2, the gate of switch PM1, the drain of switch NM1, and the inverting input terminal of comparator 1 COMP1 are connected to input node Vn, the drain of switch PM1, the gate of switch PM2, the drain of switch NM2, and the inverting input terminal of comparator 2 COMP1 are connected to input node Vp, and the source of switch PM1 and the source of switch PM2 are both connected to output node V SP The source of the switch NM1 and the source of the switch NM2 are connected to each other and grounded, the non-inverting input of the comparator COMP1 and the non-inverting input of the comparator COMP1 are grounded; the input node Vn and the input node Vp are connected to the voltage VPEH;

[0027] A comparator, which uses a common-gate amplifier structure to detect the voltage of the input node and drive the gate of the NMOS switch;

[0028] NMOS switch, used to receive the output result of the comparator, thereby controlling on or off;

[0029] PMOS switch, used to control the output of the full-wave bridge active rectifier module.

[0030] Preferably, the active diode includes: a low power comparator COMP2, a PMOS switch PM AD , a storage capacitor C RECT And digital logic circuit; the switch PM AD The drain and the inverting input of the comparator COMP2 are connected to the output node V SP connection, the switch PM AD The source of the comparator COMP2 and the non-inverting input terminal and the energy storage capacitor C RECT The upper plate of the PECT Connection, energy storage capacitor C RECT The lower plate of the comparator is grounded, the output of the comparator COMP2 is connected to the signal input of the digital logic circuit, and the output of the digital logic circuit is connected to the switch PM AD The gate connection;

[0031] A low-power comparator is used to detect the zero-crossing point of IPEH in the equivalent model of the vibration energy input source, prevent the backflow of stored charge, and input the output result into the digital logic circuit;

[0032] A digital logic circuit, configured to receive an output result of the low-power comparator and control the on or off of the PMOS switch;

[0033] PMOS switch, used to control the conduction or shutdown of the energy storage capacitor to transfer charge;

[0034] Energy storage capacitors are used to accumulate charge and store energy.

[0035] Preferably, the undervoltage lockout module includes: two voltage-dividing resistors, a hysteresis comparator, and a bandgap reference source; the two voltage-dividing resistors are resistor R1 and resistor R2,

[0036] One end of the resistor R1 is connected to the input voltage V RECT The other end of the resistor R1 is connected to one end of the resistor R2, and the other end of the resistor R2 is grounded. The middle node of the resistor R1 and the resistor R2 is connected to the non-inverting input of the hysteresis comparator, and the inverting input of the hysteresis comparator is connected to the output of the bandgap reference source. The output of the hysteresis comparator outputs EN UVLO Signal;

[0037] Voltage divider resistor, used to set and adjust the threshold voltage of the undervoltage lockout module;

[0038] Hysteresis comparator to prevent false flip jitter near the undervoltage lockout module threshold;

[0039] Bandgap reference source, used to provide reference voltage for hysteresis comparator.

[0040] Preferably, the adaptive charge transfer MPPT algorithm module includes: a sampling circuit and a control algorithm circuit; the signal output end of the control algorithm circuit is connected to the signal input end of the sampling circuit;

[0041] A sampling circuit, used for receiving and sampling the output of the full-wave bridge active rectifier module;

[0042] The control algorithm circuit is used to control the opening and closing of the switch in the drive sampling circuit and complete the adaptive sampling function.

[0043] Preferably, the sampling circuit includes: two sampling circuit switches, a sampling capacitor and a comparator COMP3; the two sampling circuit switches are switches SW RST and switch SW MPPT The lower plate of the sampling capacitor is grounded, the upper plate of the sampling capacitor is connected to the inverting input of the comparator COMP3, the output of the comparator COMP3 is connected to the input of the control algorithm circuit, and the switch SW RST One end of the sampling capacitor is connected to the upper plate, and the switch SW RST The other end is connected to the lower plate of the sampling capacitor, and the switch SW MPPT One end of the sampling capacitor is connected to the upper plate, and the switch SW MPPT The other end is connected to the non-inverting input of comparator COMP3.

[0044] Preferably, the control algorithm circuit includes: a counter and a register; the signal input end of the counter is respectively connected to the signal output end of the active diode and the signal output end of the undervoltage lockout module, the signal input end of the register is respectively connected to the signal output end of the counter and the signal output end of the sampling circuit, and the signal output end of the register is connected to the signal input end of the sampling circuit.

[0045] Compared with the prior art, the present invention has the following beneficial effects:

[0046] The present invention discloses an adaptive MPPT vibration energy harvesting and management chip based on charge transfer, which consists of a nine-phase SSHC module, a full-wave bridge active rectifier module, an active diode, an undervoltage lockout module, and an adaptive charge transfer MPPT algorithm module. The advantages of each module are as follows:

[0047] (1) In the nine-phase SSHC module, only three transmission gate switches are connected in series in the nine phases, the total series resistance is low during the charge transfer, the total time required for voltage flipping is shorter, and the flipping efficiency of the voltage at the equivalent model of the vibration energy input source can be effectively adjusted and optimized.

[0048] (2) Compared with the traditional diode rectifier circuit, the combination of the full-wave bridge active rectifier module and the active diode has a lower required conduction voltage drop, can prevent the backflow of stored charges, and has a reduced influence of reverse leakage current and reverse recovery leakage problem, and has a higher AC-to-DC rectification efficiency.

[0049] (3) The under-voltage lockout module can turn off the connected module when the input source energy is insufficient, prevent misoperation, have higher stability, and have less additional power consumption.

[0050] (4) The adaptive charge transfer MPPT algorithm module only performs fast sampling when the input condition changes, can minimize the interruption of the energy transmission path from the input to the output, thereby reducing the charge loss in the sampling stage, and can improve the sampling speed and accuracy by using the charge transfer voltage division method, and finally improve the energy conversion efficiency of the chip.

[0051] Compared with the traditional vibration energy collection and management circuit, the adaptive MPPT vibration energy collection and management chip based on charge transfer has the following advantages:

[0052] (1) Firstly, the chip has a high voltage flipping efficiency and minimizes the charge loss during energy collection. Secondly, the adaptive MPPT vibration energy collection and management chip based on charge transfer can avoid internal logic abnormalities or invalid work at low voltage, has high system stability and reliability, can reduce the need for external protection circuit, and reduces the design complexity.

[0053] (2) Secondly, the functions of the adaptive MPPT vibration energy collection and management chip based on charge transfer are realized by on-chip capacitors, which has few off-chip components, high integration, small area and low manufacturing cost.

[0054] (3) Finally, the adaptive MPPT vibration energy collection and management chip based on charge transfer works at the maximum power point, has high power conversion efficiency, and can automatically and quickly adjust the corresponding maximum power point according to the changes of the external environment, and is suitable for various vibration energy collection scenes with different characteristics. BRIEF DESCRIPTION OF DRAWINGS

[0055] Figure 1 The figure is a whole logic diagram of the adaptive MPPT vibration energy collection and management chip based on charge transfer.

[0056] Figure 2 Fig. 1 is a schematic diagram of a nine-phase SSHC module implementation scheme and control switch timing waveform; wherein,

[0057] Figure 2 Fig. 2 is a schematic diagram of a nine-phase SSHC module implementation scheme;

[0058] Figure 2 Fig. 3 is a schematic diagram of a nine-phase SSHC module control switch timing waveform.

[0059] Figure 3 Fig. 4 is a schematic diagram of a full-wave bridge active rectifier module and active diode implementation scheme.

[0060] Figure 4 Fig. 5 is a schematic diagram of a full-wave bridge active rectifier module input / output waveform and local amplification waveform; wherein,

[0061] Figure 4 Fig. 6 is a schematic diagram of a full-wave bridge active rectifier module input / output waveform;

[0062] Figure 4 Fig. 7 is a schematic diagram of a full-wave bridge active rectifier module local amplification waveform.

[0063] Figure 5 Fig. 8 is a schematic diagram of an under-voltage lockout module implementation scheme.

[0064] Figure 6 Fig. 9 is a schematic diagram of an adaptive charge transfer MPPT algorithm module implementation scheme.

[0065] Figure 7 Fig. 10 is a flow chart of an adaptive charge transfer MPPT algorithm module.

[0066] Figure 8 Fig. 11 is a schematic diagram of a comparator circuit structure in a full-wave bridge active rectifier module.

[0067] Figure 9 Fig. 12 is a schematic diagram of a hysteresis comparator circuit structure in an under-voltage lockout module.

[0068] The reference numerals in the figures are as follows: 101 is a nine-phase SSHC module, 102 is a full-wave bridge active rectifier module, 103 is an active diode, 104 is an under-voltage lockout module, and 105 is an adaptive charge transfer MPPT algorithm module. DETAILED DESCRIPTION

[0069] The present application will be further described in detail below with reference to the accompanying drawings. The present embodiment is implemented on the premise of the technical scheme of the present application, and a detailed implementation manner is given, but the protection scope of the present application is not limited to the following embodiments. Specific implementation manner one

[0071] like Figure 1 As shown, an adaptive MPPT vibration energy harvesting and management chip based on charge transfer includes: a nine-phase SSHC module 101, a full-wave bridge active rectifier module 102, an active diode 103, an undervoltage lockout module 104, and an adaptive charge transfer MPPT algorithm module 105;

[0072] The signal output end of the vibration energy input source equivalent model is respectively connected to the signal input end of the nine-phase SSHC module 101 and the signal input end of the full-wave bridge active rectifier module 102. The signal output end of the nine-phase SSHC module 101 is connected to the signal input end of the full-wave bridge active rectifier module 102. The signal output end of the full-wave bridge active rectifier module 102 is respectively connected to the signal input end of the active diode 103 and the signal input end of the adaptive charge transfer MPPT algorithm module 105. The signal output end of the active diode 103 is respectively connected to the signal input end of the nine-phase SSHC module 101, the signal input end of the undervoltage lockout module 104 and the signal input end of the adaptive charge transfer MPPT algorithm module 105. The signal output end of the undervoltage lockout module 104 is connected to the signal input end of the adaptive charge transfer MPPT algorithm module 105. The signal output ends of the active diode 103, the undervoltage lockout module 104 and the adaptive charge transfer MPPT algorithm module 105 are all connected to the signal input end of the battery management system.

[0073] like Figure 2 As shown, the nine-phase SSHC module 101 is composed of eleven transmission gate switches (including two switches SW P , two switches SW N , switch SW1, switch SW2, switch SW3, two switches SW4, two switches SW5), three flip capacitors (including: flip capacitor C2, flip capacitor C3, flip capacitor C4) and a switch logic clock circuit. The circuit structure of the nine-phase SSHC module 101 is as follows Figure 2 As shown in (a), the switch logic clock circuit provides the control signal for the transmission gate switch. The switch control signal timing waveform is as follows: Figure 2 (b) The nine-phase SSHC module 101 has nine phases ( ) can effectively adjust the voltage V across PEH (Piezoelectric Energy Harvesting) PEH After the chip is connected to the equivalent model of the vibration energy input source, I PEH First, C PEH Charging, it can be considered that the initial input charge is accumulated in C PEH The periodic clock of each transmission gate switch is generated by the switch logic clock circuit.PEH When the zero point of RECT It is provided as an enable signal to the switch logic clock circuit to generate various control signals for the transmission gate switches, and the transmission gate switches are opened and closed in sequence.

[0074] The working process of the nine-phase SSHC module 101 can be divided into three stages: initial stage, short circuit stage and reconstruction stage. The initial stage is the damping stage ( ), when the module is in When the two switches SW P First, switch SW1, switch SW2, and switch SW3 are closed in sequence, and the flip capacitor C1 (flip capacitor C2 and flip capacitor C3 are connected in series), flip capacitor C2, and flip capacitor C3 are connected to the circuit and C PEH In parallel, Phase, the two switches SW P Open, the two switches SW4 are closed, flipping the capacitors C4 and C PEH In parallel, within each phase C PEH By connecting in parallel with the corresponding flip capacitor, the charge is transferred to complete the discharge. In the damping stage, when the nine-phase SSHC module 101 in the nth phase is stable, the voltage V d (n) = V d (n-1)C PEH / (C PEH +C n The nine-phase SSHC module 101 then enters the second stage, which is the short-circuit stage ( ), close the two SW P and two SW N , to completely eliminate C PEH The third stage is the reconstruction stage ( ), during this phase the capacitor is flipped to C PEH Transfer charge, In phase, except for the two switches SW5 that are closed, the other switches are open, and C PEH The upper and lower plates of the flip capacitor C4 are connected in reverse parallel. When the two switches SW N Close, switch SW3, switch SW2, and switch SW1 are closed in sequence, respectively connecting the plates of flip capacitor C3, flip capacitor C2, and flip capacitor C1 to C PEH In reverse parallel, C PEH Reverse charging, in the reconstruction phase, the voltage V b (n) = V b (n-1)C PEH +V d (10-n)C10-n / (C PEH +C 10-n ), after one cycle of voltage reversal is completed, V PEH The voltage value is V B In the nine phases of the nine-phase SSHC module 101, there are only three transmission gate switches in series at most, which helps to PEH During the charge transfer between the flip capacitor and the flip capacitor, the total series resistance is controlled to a low value, thereby limiting the total time (RC) required for voltage flipping. Generally, in order to balance the impact between area cost and flipping efficiency, the value of flip capacitor C1 (flip capacitor C2 and flip capacitor C3 in series) is set to 4 to 6 times the parasitic capacitance of the equivalent model of the vibration energy input source during the design process, that is, C2 + C3 = (4 to 6) C PEH The nine-phase SSHC module 101 can limit the total time required for voltage switching and optimize voltage switching efficiency.

[0075] The input of the full-wave bridge active rectifier module 102 is connected to the output of the vibration energy source equivalent model and the nine-phase SSHC module 101. The output of the full-wave bridge active rectifier module 102 is provided to the active diode 103 for energy collection, or is input as an open-circuit voltage to the adaptive charge transfer MPPT algorithm module 105. By alternately opening and closing the switch, the rectification function of converting AC input to DC output is completed. Figure 3 As shown, the full-wave bridge active rectifier module 102 is composed of two comparators COMP1, two NMOS switches (NM1, NM2) and two PMOS switches (PM1, PM2). PEH The rebuild phase of the flip starts working when V PEH In the damping stage, the full-wave bridge active rectifier module 102 is in a dormant state. Assume that the input state of the full-wave bridge active rectifier module 102 circuit is that Vn is in the negative half cycle, Vp is in the positive half cycle, PM1 is turned on, and the comparator compares the input voltage with the ground potential. The output result of COMP1 on the left is high, which turns NM1 on and NM2 off. Therefore, only the positive half cycle of the input source is transmitted to the output node V SP , completing a half-wave rectification. When the input Vn is in the positive half cycle and Vp is in the negative half cycle, PM2 is turned on, and the comparator compares the input voltage with the ground potential. The output result of COMP1 on the right is high, which turns on NM2 and completes another half-wave rectification. Therefore, the output node V SP Always connected to the positive input, V PEH Complete the rectification process from AC to DC. In order to meet the requirement of comparing with zero potential, the comparator in the full-wave bridge active rectifier module 102 adopts a common gate amplifier structure. The common gate amplifier circuit structure is as follows: Figure 8As shown, the specific connection method is as follows: the source of NM3 is connected to one end of the resistor R0, the other end of R0 is grounded to provide bias current, the gate of NM3 is connected to the gate of NM2, the drain of NM3 is connected to the drain of PM4, the gate of NM2 is connected to the drains of NM2 and PM5 respectively, the source of NM2 is grounded, the drain of PM4 is connected to the gate of PM4, the gate of PM4 is connected to the gates of PM5, PM0, and PM1, the source of PM4 is connected to the drain of PM6, the source of PM5 is connected to the drain of PM7, the drain of PM6 is connected to the gate of PM6, the gate of PM6 is connected to the gates of PM7, PM2, and PM3, and the sources of PM6 and PM7 are connected to the highest potential V RECT , the sources of NM0 and NM1 serve as two input terminals, the source of NM0 serves as the inverting input terminal Vin-, the source of NM1 serves as the non-inverting input terminal Vin+ and is always grounded, the gate of NM0 is connected to the gate of NM1, the gate of NM0 is connected to the drain of NM0, the drain of NM0 is connected to the drain of PM0, the source of PM0 is connected to the drain of PM2, and the sources of PM2 and PM3 are connected to the highest potential V RECT , the drain of PM3 is connected to the source of PM1, the drain of PM1 is connected to the drain of NM1, the drain of NM1 is connected to the input of the inverter chain, the source of the inverter is connected to the current limiting resistor R1, and the output of the inverter chain is used as the output of the comparator V OUT , the substrates of NM0, NM1, NM2, and NM3 are all grounded, and the substrates of PM0, PM1, PM2, PM3, PM4, PM5, PM6, and PM7 are all connected to the highest potential V RECT .

[0076] The input of the active diode 103 is connected to the output of the full-wave bridge active rectifier module 102, as shown in FIG. Figure 3 As shown, the active diode 103 is composed of a low power comparator COMP2, a PMOS switch (switch PM AD ), a storage capacitor C RECT and digital logic circuit; the output of the low-power comparator controls the state of the PMOS switch after passing through the digital logic circuit. The active diode 103 takes time t from input to stable output. n After the output is stable, the charge storage energy is accumulated on the energy storage capacitor, and the zero crossing point of IPEH is detected by the low-power comparator to prevent the stored charge from flowing back. The output is provided to the nine-phase SSHC module 101 and the battery management system. When the output V RECT =V B / 2+V OC When , the vibration energy input source equivalent model and the full-wave bridge active rectifier module 102 can provide maximum power to the load.

[0077] Input current I of the equivalent model of vibration energy input source PEH、Input voltage V PEH and the output voltage of the active rectifier part V RECT Waveform Figure 4 As shown in (a), a cycle can be divided into the MPPT stage, the voltage reversal stage and the energy collection stage, where the MPPT stage lasts for T MPPT is half of the entire period T, the nine-phase SSHC module 101 works to cause V PEH When the voltage is reversed and the nine-phase SSHC module 101 starts to work, the input voltage V PEH The value is V D , the local amplified waveforms of each phase during the flipping process are as follows Figure 4 As shown in (b), after the voltage reversal is completed, the input voltage V PEH The value of V B , V PEH From V B Reaching a stable output value V RECT It takes some time n , V RECT and V B The voltage difference between them is △V, and the input current I PEH Charge is injected into the rectifier module, but since it has not entered the energy collection stage, there is a certain amount of input charge loss.

[0078] When the low power comparator COMP2 detects I PEH After the zero crossing point of V, the digital logic circuit turns off the PMOS switch in time to prevent the stored charge from flowing back. PEH During the flipping process, the active diode 103 should be disconnected from the PEH to ensure that C PEH The charge between the flip capacitor and the capacitor can be transferred correctly to prevent C RECT When the rectification phase starts, the output EN of the low power comparator RECT It is low level and outputs SW after passing through the digital logic circuit. AD PM AD Turn on, V SP The charge is transferred and stored to C RECT , V RECT Gradually increases. Since the V PEH Voltage equal to V B , V SP From V B Reach V RECT It takes some time n , after reaching V RECT Then it enters the energy collection stage, so the charge loss formula in one cycle is as follows: Q LOSS =2C PEH△V=2C PEH (V RECT -V B ). When I PEH When reaching the zero point, V SP The output of the half-wave cycle begins to be rectified again, causing V RECT The node voltage is greater than V SP , EN RECT Goes high, SW AD Turn off PM AD , to prevent C RECT Reverse discharge causes V PEH When the active diode 103 is in an open circuit, V RECT =V OC , then the total charge provided by PEH in one cycle is Q PEH =4C PEH V OC , so the net charge Q collected by the full-wave bridge active rectifier module 102 RECT =Q PEH -Q LOSS =2C PEH (2V OC -(V RECT -V B )), the output power P of the full-wave bridge active rectifier module 102 RECT =2C PEH f PEH (2V OC -(V RECT -V B ))V RECT , where f PEH is the vibration frequency of PEH, so when V RECT =V B / 2+V OC When the vibration energy input source equivalent model and the full-wave bridge active rectifier module 102 can provide the maximum power to the load, V RECT The corresponding value is the maximum power point voltage V when the chip is working. MPP , then V MPP =V B / 2+V OC .

[0079] The input of the undervoltage lockout module 104 is connected to the output of the active diode 103, which is then divided by a resistor and compared with the reference voltage. The output of the undervoltage lockout module 104 serves as an enable signal, connecting the adaptive charge transfer MPPT algorithm module 105 and the battery management system. When the input source energy is insufficient, the enable signal shuts down the connected modules, putting the chip into undervoltage lockout mode to prevent malfunctions that cause additional power consumption. Figure 5As shown, the undervoltage lockout module 104 consists of two voltage-dividing resistors R1 and R2, a hysteresis comparator and a bandgap reference source. The bandgap reference source provides a reference voltage for the hysteresis comparator. The hysteresis comparator has a hysteresis interval to prevent false flip jitter near the threshold. When the input voltage V RECT When the lower threshold is not reached, the output of the hysteresis comparator puts the subsequent circuit into a dormant lock state to prevent the chip from malfunctioning and causing additional power consumption. The input energy is stored in the capacitor C RECT , until V RECT The threshold of the hysteresis comparator is about 300mV, which prevents V RECT When the module is near the threshold, it will generate false flip jitter. REF Generated by the bandgap reference source, when the input energy is low, the output voltage V RECT The voltage divided by the voltage divider resistors R1 and R2 is V FB At this time, it is less than V REF , the hysteresis comparator outputs a low level as the enable signal EN UVLO , turn off the adaptive charge transfer MPPT algorithm module 105 and the battery management system. At this time, the chip is in undervoltage lockout mode, and the input charge is C RECT When V RECT When it rises above the preset high threshold, V FB Greater than V REF , hysteresis comparator output enable signal EN UVLO When the voltage is high, the undervoltage lockout mode is turned off, and the adaptive charge transfer MPPT algorithm module 105 and the battery management system start working. The hysteresis comparator uses an internal positive feedback loop to achieve a hysteresis effect and adopts a comparator structure with a cross-coupled differential pair. The circuit structure of the hysteresis comparator is as follows: Figure 9 As shown, the specific connection method is as follows: the drain of PM3 is connected to the current source I bias , current source I bias The other end of PM3 is grounded, the gate of PM3 is connected to the drain of PM3, and the source of PM3 is connected to the highest potential V RECT , the gate of PM2 is connected to the gate of PM3, and the source of PM2 is connected to the highest potential V RECT, the drain of PM2 is connected to the source of PM0 and PM1, the gates of PM0 and PM1 serve as two input terminals, the gate of PM0 serves as the inverting input terminal V-, the gate of PM1 serves as the non-inverting input terminal V+, the drain of PM0 is connected to the drains of NM0 and NM2, the drain of PM0 is connected to the gates of NM0, NM1 and NM4, the drain of PM1 is connected to the drains of NM1 and NM3, the drain of PM1 is connected to the gates of NM2, NM3 and NM5, the sources of NM0, NM1, NM2, NM3, NM4 and NM5 are grounded, the drain of NM4 is connected to the drain of PM4, the drain of PM4 is connected to the gate of PM4, the gate of PM4 is connected to the gate of PM5, and the sources of PM4 and PM5 are connected to the highest potential V RECT , the drain of PM5 is connected to the drain of NM5, the drain of NM5 is connected to the input of the inverter chain, and the output of the inverter chain is used as the output of the comparator V OUT , the substrates of NM0, NM1, NM2, NM3, NM4, and NM5 are all grounded, and the substrates of PM0, PM1, PM2, PM3, PM4, and PM5 are all connected to the highest potential V RECT .

[0080] like Figure 6 As shown, the adaptive charge transfer MPPT algorithm module 105 includes a sampling circuit and a control algorithm circuit. The sampling circuit has two switches, a sampling capacitor and a comparator, and the control algorithm circuit is composed of a counter and a register. The input of the sampling circuit is connected to the output of the full-wave bridge active rectifier module 102. The input enable signal of the control algorithm circuit is provided by the active diode 103 and the undervoltage lockout module 104. The output of the control algorithm circuit drives the sampling switch to control the opening and closing. The control algorithm uses monitoring t n The change of t completes the adaptive sampling function, n It has a certain tolerance limit. When the input source amplitude changes slightly and is within the limit, MPPT re-sampling will not be triggered, preventing the chip from frequently triggering sampling due to small errors. When the input source amplitude changes significantly beyond the preset range, the adaptive control algorithm circuit will enable the chip to perform a new cycle of MPPT sampling on the current open circuit voltage, which can minimize the energy loss from I PEH to C L The interruption of the transmission path reduces the charge loss in the MPPT sampling phase. Based on the charge transfer principle on the sampling capacitor and parasitic capacitor, the following formula is used:

[0081] V MPPT =(2C PEH (V B / 2+V OC )) / (C PEH +C MPPT )

[0082] Among them, VMPPT is the voltage value obtained by the sampling circuit in the adaptive charge transfer MPPT algorithm module 105 after sampling and voltage division, C PEH is the parasitic capacitance value in the equivalent model of the vibration energy input source, V B The input voltage value provided by the equivalent model of the vibration energy input source after the voltage reversal of one cycle is completed, V OC is the output voltage value of the full-wave bridge active rectifier module 102 when the active diode 103 is in an open circuit, C MPPT is the sampling circuit value of the sampling circuit in the adaptive charge transfer MPPT algorithm module 105;

[0083] It can realize fast sampling of open circuit voltage and improve sampling speed and accuracy. The V MPPT The output is ultimately sent to the battery management system. A charge-transfer-based adaptive MPPT vibration energy harvesting and management chip completes the rectification from AC input to DC output, and obtains the maximum power point voltage corresponding to the current input conditions, which is then provided to the battery management system to power the load.

[0084] When the amplitude of the input source changes slightly, the change is ignored and the V of the previous input stage is maintained. MPP When the input source amplitude changes greatly, it automatically determines and calculates the maximum power point voltage V of the adaptive MPPT vibration energy collection and management chip based on charge transfer. MPP , complete the chip V MPP Before the sampling phase of the adaptive charge transfer MPPT algorithm module 105 begins, the switch SW MPPT Open, V SP Rising in C PEH The accumulated charge Q RST =V B C PEH , SW RST Closed, sampling capacitor C MPPT Short-circuit discharge reset voltage to prevent the accumulated charge from affecting the sampling voltage V MPPT When the adaptive charge transfer MPPT algorithm module 105 is in the sampling phase, SW MPPT Closed, SW RST Open, C MPPT with C PEH Parallel, C eq =C PEH +C MPPT , so in C PEH The charge accumulated on C MPPT The comparator compares V SP and V MPPT Determine the open circuit voltage VOC sampling is completed, output EN MPPT_ST pass through the control algorithm circuit to make SW MPPT open, SW RST close, end the MPPT sampling process. At the end of sampling, the charge of C PEH is transferred to the charge of C MPPT . The charge of C MPPT = Q RST + Q PEH / 2. In this stage, the active diode 103 is turned off, the energy collection in half of the vibration period is suspended, and the charge of C RECT interferes with the charge transfer between C MPPT and C PEH . The chip is in the open-circuit state, V SP corresponds to the open-circuit input voltage V OC , and V MPPT = V MPPT / 2 + V MPPT . The calculation formula is as follows:

[0085] V eq = Q PEH / C B = (2C OC (V PEH / 2 + V MPPT )) / (C MPPT + C PEH )

[0086] take C MPPT = C B , and V OC = V MPP / 2 + V PEH , which is equal to the maximum power point voltage V n of the chip in operation. It can be input into the battery management system as a reference voltage, thereby completing the maximum power extraction of the vibration input energy. When the adaptive MPPT vibration energy collection and management chip is in a stable state, the amplitude of I PEH is constant, and therefore the t n of the active diode 103 is also constant. Different amplitudes of I n have corresponding stable values of t PEH . The adaptive charge transfer MPPT algorithm module 105 uses the change of t OC to complete the adaptive sampling function, so that the chip only performs V UVLO fast sampling when the amplitude of I PEH changes, thereby reducing the sampling time and power loss. After the chip is closed in the under-voltage lockout mode, EN RECTThe counter counts until it reaches a preset value N, which depends on the excitation frequency of PEH. L To minimize the discontinuous energy transfer between nodes and maximize the efficiency of MPPT, N is set as 200. Figure 7 As shown in I PEH When the number of zero crossings reaches N, the counter outputs EN MPPT The module is forced to perform the first MPPT sampling. At the same time, the counter records the duration of MPPT T / 2 and stores it in the register. PEH At the zero crossing point, the counter measures t n And store it in the register as the initial t0. Then the counter waits for the zero crossing point of the next cycle and measures the corresponding t n , t n and t0-k L and t0-k H For comparison, k L and k H is the preset threshold parameter, which is t n Provide a certain tolerance limit, within which I can be ignored PEH changes, the register outputs the EN RST Make SW RST Close, EN SAMP Make SW MPPT When it is turned on, there is no need to re-sample the MPPT, which can prevent the chip from frequently triggering sampling due to minor errors. PEH Increase or decrease leads to t n When the voltage changes outside the tolerance range, the module will start a new MPPT cycle, and SW MPPT Closed, SW RST Open, the counter re-measures T / 2 and t0 at this time and stores them, and re-stores the new T / 2. To prevent I PEH Too small, t n Timeout, failure to detect the zero crossing point leads to internal logic disorder of the chip. In this case, when the counter measures t n When the stored value T / 2 is reached, a new cycle of MPPT sampling is forced. The adaptive MPPT algorithm module based on charge transfer can minimize the energy from I PEH to C L The interruption of the transmission path reduces the charge loss in the MPPT sampling stage, improves the sampling speed and accuracy, and ultimately improves the energy conversion efficiency of the chip.

[0087] The above merely describes preferred specific embodiments of the present application, which are based on different implementations of the overall concept of the present application, and the protection scope of the present application is not limited thereto. Any changes or replacements that are easily conceived by those skilled in the art within the technical scope disclosed by the present application shall be covered by the protection scope of the present application. Therefore, the protection scope of the present application should be subject to the protection scope of the claims.

Claims

1. An adaptive MPPT vibration energy collection and management chip based on charge transfer, characterized in that: include: A nine-phase SSHC module (101), a full-wave bridge active rectifier module (102), an active diode (103), an undervoltage lockout module (104), and an adaptive charge transfer MPPT algorithm module (105); The signal output end of the vibration energy input source equivalent model is respectively connected to the signal input end of the nine-phase SSHC module (101) and the signal input end of the full-wave bridge active rectifier module (102), the signal output end of the nine-phase SSHC module (101) is connected to the signal input end of the full-wave bridge active rectifier module (102), the signal output end of the full-wave bridge active rectifier module (102) is respectively connected to the signal input end of the active diode (103) and the signal input end of the adaptive charge transfer MPPT algorithm module (105), the active diode (1 The signal output end of the active diode (103) is connected to the signal input end of the nine-phase SSHC module (101), the signal input end of the undervoltage lockout module (104) and the signal input end of the adaptive charge transfer MPPT algorithm module (105), respectively. The signal output end of the undervoltage lockout module (104) is connected to the signal input end of the adaptive charge transfer MPPT algorithm module (105). The signal output ends of the active diode (103), the undervoltage lockout module (104) and the adaptive charge transfer MPPT algorithm module (105) are all connected to the signal input end of the battery management system.

2. The charge transfer-based adaptive MPPT vibration energy collection and management chip according to claim 1, characterized in that: A nine-phase SSHC module (101) is used to control the total series resistance value of the capacitance of the equivalent model of the vibration energy input source and the flip capacitor in the nine-phase SSHC module (101) during the charge transfer period; A full-wave bridge active rectifier module (102) for converting an AC input signal into a DC output signal; An active diode (103) for processing an output signal of the energy harvesting full-wave bridge active rectifier module (102); An undervoltage lockout module (104) is used to monitor an input voltage threshold and control the adaptive charge transfer MPPT algorithm module (105) and the battery management system to sleep or start working; The adaptive charge transfer MPPT algorithm module (105) is used to determine and calculate the corresponding maximum power point voltage when the input current amplitude of the vibration energy input source equivalent model changes, and to adaptively sample and control the maximum power point voltage; the maximum power point voltage obtained by sampling is calculated as follows: In MPPT =(2C PEH (In) B / 2+V OC )) / (C PEH +C MPPT ) Among them, V MPPT is the voltage value obtained by the sampling circuit in the adaptive charge transfer MPPT algorithm module (105) after sampling and voltage division, C PEH is the parasitic capacitance value in the equivalent model of the vibration energy input source, V B The input voltage value provided by the equivalent model of the vibration energy input source after the voltage reversal of one cycle is completed, V OC is the output voltage value of the full-wave bridge active rectifier module (102) when the active diode (103) is in an open circuit, C MPPT is a sampling circuit value of a sampling circuit in an adaptive charge transfer MPPT algorithm module (105); The battery management system is used to further control the outputs of the active diode (103), the undervoltage lockout module (104), and the adaptive charge transfer MPPT algorithm module (105), and ultimately supply power to the load.

3. The charge transfer-based adaptive MPPT vibration energy collection and management chip according to claim 1, characterized in that: The nine-phase SSHC module (101) comprises: eleven transmission gate switches, three flip capacitors and a switch logic clock circuit; the eleven transmission gate switches are respectively two switches SW P , two switches SW N , switch SW1, switch SW2, switch SW3, two switches SW4 and two switches SW5; the three flip capacitors are flip capacitor C2, flip capacitor C3 and flip capacitor C4; The signal output end of the switch logic clock circuit is connected to each transmission gate switch; the two switches SW P With the two switches SW N After one-to-one correspondence and series connection, branches are obtained respectively. The two switches SW4 and the two switches SW5 are connected in series one-to-one to obtain branches respectively. The four branches are connected in parallel. The upper plate of the flip capacitor C2 is connected to the switch SW P With switch SW N In one of the series branches, the lower plate of the flip capacitor C2 is connected to one end of the switch SW1, the other end of the switch SW1 is connected to the upper plate of the flip capacitor C3, and the lower plate of the flip capacitor C3 is connected to the switch SW P With switch SW N Another branch in series; one end of the switch SW2 is connected between the switch SW1 and the flip capacitor C2, and the other end is connected to the lower plate of the flip capacitor C3; one end of the switch SW3 is connected to the upper plate of the flip capacitor C2, and the other end is connected between the switch SW1 and the flip capacitor C2; the upper plate of the flip capacitor C4 is connected to one of the branches connected in series with the branch switches SW4 and SW5, and the lower plate of the flip capacitor C4 is connected to the other branch connected in series with the branch switches SW4 and SW5; A transmission gate switch for controlling the total series resistance of the flip capacitor during charge transfer; Flip capacitor, used to store and transfer charge; The switching logic clock circuit is used to provide control signals for the transmission gate switches.

4. The charge transfer-based adaptive MPPT vibration energy collection and management chip according to claim 1, characterized in that: The full-wave bridge active rectifier module (102) comprises: two comparators, two NMOS switches, and two cross-coupled PMOS switches; the two comparators are respectively comparator 1 COMP1 and comparator 2 COMP1; the two NMOS switches are respectively switch NM1 and switch NM2; the two cross-coupled PMOS switches are respectively switch PM1 and switch PM2; The gate of switch NM1 is connected to the output terminal of comparator 1 COMP1, the gate of switch NM2 is connected to the output terminal of comparator 2 COMP1, the drain of switch PM2, the gate of switch PM1, the drain of switch NM1, and the inverting input terminal of comparator 1 COMP1 are connected to input node Vn, the drain of switch PM1, the gate of switch PM2, the drain of switch NM2, and the inverting input terminal of comparator 2 COMP1 are connected to input node Vp, and the source of switch PM1 and the source of switch PM2 are both connected to output node V SP The source of the switch NM1 and the source of the switch NM2 are connected to each other and grounded, the non-inverting input of the comparator COMP1 and the non-inverting input of the comparator COMP1 are grounded; the input node Vn and the input node Vp are connected to the voltage VPEH; A comparator, which uses a common-gate amplifier structure to detect the voltage of the input node and drive the gate of the NMOS switch; NMOS switch, used to receive the output result of the comparator, thereby controlling on or off; The PMOS switch is used to control the output of the full-wave bridge active rectifier module (102).

5. The charge transfer-based adaptive MPPT vibration energy collection and management chip according to claim 4, characterized in that: The active diode (103) comprises: a low-power comparator COMP2, a PMOS switch PM AD , a storage capacitor C RECT And digital logic circuit; the switch PM AD The drain and the inverting input of the comparator COMP2 are connected to the output node V SP connection, the switch PM AD The source of the comparator COMP2 and the non-inverting input terminal and the energy storage capacitor C RECT The upper plate is connected to the voltage V PECT Connection, energy storage capacitor C RECT The lower plate of the comparator is grounded, the output of the comparator COMP2 is connected to the signal input of the digital logic circuit, and the output of the digital logic circuit is connected to the switch PM AD The gate connection; A low-power comparator is used to detect the zero-crossing point of IPEH in the equivalent model of the vibration energy input source, prevent the backflow of stored charge, and input the output result into the digital logic circuit; A digital logic circuit, configured to receive an output result of the low-power comparator and control the on or off of the PMOS switch; PMOS switch, used to control the conduction or shutdown of the energy storage capacitor to transfer charge; Energy storage capacitors are used to accumulate charge and store energy.

6. The charge transfer-based adaptive MPPT vibration energy collection and management chip according to claim 1, characterized in that: The undervoltage lockout module (104) comprises: two voltage-dividing resistors, a hysteresis comparator, and a bandgap reference source; the two voltage-dividing resistors are resistor R1 and resistor R2, respectively. One end of the resistor R1 is connected to the input voltage V RECT The other end of the resistor R1 is connected to one end of the resistor R2, and the other end of the resistor R2 is grounded. The middle node of the resistor R1 and the resistor R2 is connected to the non-inverting input of the hysteresis comparator, and the inverting input of the hysteresis comparator is connected to the output of the bandgap reference source. The output of the hysteresis comparator outputs EN UVLO Signal; Voltage divider resistor, used to set and adjust the threshold voltage of the undervoltage lockout module; Hysteresis comparator to prevent false flip jitter near the undervoltage lockout module threshold; Bandgap reference source, used to provide reference voltage for hysteresis comparator.

7. The charge transfer-based adaptive MPPT vibration energy collection and management chip according to claim 1, characterized in that: The adaptive charge transfer MPPT algorithm module (105) comprises: a sampling circuit and a control algorithm circuit; the signal output end of the control algorithm circuit is connected to the signal input end of the sampling circuit; A sampling circuit, used for receiving the output of the full-wave bridge active rectifier module (102) and performing sampling; The control algorithm circuit is used to control the opening and closing of the switch in the drive sampling circuit and complete the adaptive sampling function.

8. The charge transfer-based adaptive MPPT vibration energy collection and management chip according to claim 7, characterized in that: The sampling circuit includes: two sampling circuit switches, a sampling capacitor and a comparator COMP3; the two sampling circuit switches are switches SW RST and switch SW MPPT The lower plate of the sampling capacitor is grounded, the upper plate of the sampling capacitor is connected to the inverting input of the comparator COMP3, the output of the comparator COMP3 is connected to the input of the control algorithm circuit, and the switch SW RST One end of the sampling capacitor is connected to the upper plate, and the switch SW RST The other end is connected to the lower plate of the sampling capacitor, and the switch SW MPPT One end of the sampling capacitor is connected to the upper plate, and the switch SW MPPT The other end is connected to the non-inverting input of comparator COMP3.

9. The charge transfer-based adaptive MPPT vibration energy collection and management chip according to claim 8, characterized in that: The control algorithm circuit includes: a counter and a register; the signal input end of the counter is respectively connected to the signal output end of the active diode (103) and the signal output end of the undervoltage lockout module (104); the signal input end of the register is respectively connected to the signal output end of the counter and the signal output end of the sampling circuit; and the signal output end of the register is connected to the signal input end of the sampling circuit.

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