A compact W-band filter power divider with reversed output characteristics

Abstract

The application discloses a compact W-band filter power divider with reverse output characteristics, comprising a band-pass filter network, an isolation-power distribution unit and an output coupling structure. After the input signal is filtered by the band-pass filter network, it enters the isolation-power distribution unit. The energy is coupled to the upper and lower symmetrical output channels through the input channel in the center of the cavity, forming an equal amplitude coupling mode, and then entering the output coupling structure. In the output coupling structure, the directional rotation of the curved waveguide in the two output channels introduces the directionality rotation, so that the TE 10 The main mode is mirror flipped in the process of propagating in the curved channel, and the inherent odd mode excitation characteristics in the superposition coupling channel are superimposed, so that a stable 180-degree phase difference is finally generated at the two output ports. The structure can realize the cooperative characteristics of equal amplitude power distribution, 180-degree output phase difference, deep out-of-band suppression and high isolation output, and meets the integration demand of a high-performance millimeter wave subsystem.

Description

Technical Field

[0001] This invention relates to a waveguide device, and more particularly to a filter power divider. Background Technology

[0002] The W-band (75–110 GHz), as an important component of the terahertz frequency band, boasts advantages such as abundant spectrum resources, high spatial resolution, and strong penetration capabilities, and is widely used in high-frequency systems such as high-resolution imaging, millimeter-wave communication, radar detection, and security scanning. In these systems, passive components such as power dividers and filters are indispensable basic components in the front-end module, and their performance directly affects the system's signal integrity, spectrum utilization efficiency, and anti-interference capability.

[0003] Traditional W-band power dividers typically employ Wilkinson, T-type, or branch-line topologies. While these achieve power sharing and good port matching, they generally suffer from insufficient out-of-band rejection, significant deficiencies in port isolation, and inadequate control of out-of-band parasitic responses. With the increasing channel density and spectral complexity in high-frequency communication systems, traditional single-function devices are struggling to meet the growing multi-dimensional performance demands. In recent years, the functions of filters and power dividers have gradually merged, giving rise to integrated structures with frequency selectivity and power distribution capabilities—filtering power dividers (FPDs). These devices embed resonant units or coupling structures within the power distribution path, introducing bandpass or bandstop filtering characteristics while achieving power distribution. This not only helps reduce insertion loss caused by device cascading but also enables fine-tuning of the spectrum and effective suppression of parasitic signals.

[0004] Research on FPDs has made significant progress in recent years in areas such as device topology, transmission zero construction, out-of-band selectivity enhancement, and phase consistency control. However, achieving high performance of FPD structures in the W-band still faces several key engineering challenges: First, regarding out-of-band suppression, common design methods include introducing multi-order resonators, interleaved coupling units, or defective ground structures (DGS) to construct multiple transmission zeros outside the target frequency band, enhancing spectral selectivity. However, due to the high frequency and short wavelength of the W-band, the required resonant structure has extremely small physical dimensions, and its performance is highly dependent on manufacturing precision and material properties. Traditional distributed parameter resonators in this band are often significantly affected by conductor losses, parasitic effects, and contact interface errors, making it difficult to obtain a high-quality factor (Q) filtering response. At the same time, the ability to control transmission zeros is limited by structural symmetry and coupling mechanisms, resulting in limited design freedom and optimization space. Second, to improve the isolation between output ports, existing FPD designs often employ structures such as power dissipation resistors, reverse feed cavities, or balanced stubs to suppress reverse coupling of non-ideal modes. However, in the W-band, high-frequency signals are extremely sensitive to phase and amplitude errors. Traditional isolation methods often introduce additional insertion losses while failing to maintain phase consistency. Simultaneously, reverse coupling structures can disrupt circuit symmetry, leading to phase shifts between output signals. Furthermore, due to the extreme sensitivity of electromagnetic fields to structural disturbances at high frequencies, the process adaptability and stability of such isolation structures in actual circuit boards or chip packaging face severe challenges. Additionally, from a device integration perspective, existing W-band FPDs are mostly simple extensions of low-frequency designs, employing cascaded filters and power dividers. While possessing certain bandpass characteristics, they generally suffer from problems such as superimposed insertion losses, large structures, and module redundancy, making it difficult to meet the demands of modern high-frequency systems requiring high integration, low power consumption, and lightweight design. Some integrated designs, while possessing certain integration functions in their structure, have limited filtering response, limited bandwidth coverage, and lack flexibility in multi-band conformal designs.

[0005] In summary, the engineering implementation of W-band FPDs is still constrained by performance bottlenecks in multiple dimensions, mainly including: 1) weak transmission null control capability and lack of high-degree-of-freedom structures to effectively configure the position and number of nulls, resulting in a narrow out-of-band suppression range and difficulty in coping with complex electromagnetic interference environments; 2) the port isolation structure has insertion loss and non-ideal phase problems, which cannot simultaneously meet the requirements of high isolation and phase balance; 3) large structural scalability and manufacturing tolerance, relying heavily on fine processing technology, which limits practicality and repeatability; 4) low integration, large size, bulkiness, and poor functional reusability, which is not conducive to the adaptation of modern systems to the trend of multi-functional integration of devices. Summary of the Invention

[0006] Purpose of the invention: To address the aforementioned issues in the prior art, this invention proposes a compact W-band filter power divider with inverted output characteristics, which solves the problems of insufficient out-of-band suppression, low port isolation, and inadequate phase control capability in existing W-band FPDs.

[0007] Technical solution: A compact W-band filter power divider with inverted output characteristics, comprising: one input port, two output ports, a bandpass filter network, an isolation-power distribution unit, and an output coupling structure;

[0008] The bandpass filter network is a cavity structure, including a central resonant unit and two stepped impedance transformation sections symmetrically connected to both ends of the resonant unit; the stepped impedance transformation section on the left is connected to the input port.

[0009] The isolation-power distribution unit includes a cavity structure formed by a base plate and a cover plate. The cavity structure is divided into a central input channel and an upper channel and a lower channel symmetrically distributed on the upper and lower sides of the input channel. The starting end of the input channel is connected to the stepped impedance transformation section on the right side of the bandpass filter network. Vertical coupling paths are provided between the input channel and the upper and lower channels, respectively.

[0010] The output coupling structure includes two symmetrical arc-shaped transition structures. The starting ends of the two arc-shaped transition structures are respectively connected to the ends of the upper channel and the lower channel, and the ends of the two arc-shaped transition structures are respectively connected to the two output ports. The curved waveguides of the two arc-shaped transition structures are provided with directional rotation that causes the main mode to undergo a mirror-reversal of the spatial electric field direction during propagation in the curved waveguide.

[0011] Furthermore, the resonant unit is composed of multiple sets of metal rectangular pillars arranged in the cavity, each set of metal rectangular pillars being composed of several metal rectangular pillars evenly spaced along the length of the cavity; one set of metal rectangular pillars is arranged along the axis of the cavity, and the remaining sets of metal rectangular pillars are symmetrically distributed on both sides of the set.

[0012] Furthermore, in the isolation-power distribution unit, the input channel is separated from the upper channel and the lower channel by a metal partition, a plurality of metal pillars evenly spaced, and another metal partition, respectively, from the beginning to the end of the channel; wherein, the plurality of metal pillars evenly spaced serve as the vertical coupling path.

[0013] Furthermore, the input port and both output ports use standard WR10 waveguides.

[0014] Furthermore, in the resonant unit, each metal rectangular pillar is arranged perpendicular to the length direction of the cavity, with the bottom end of the metal rectangular pillar connected to the cavity wall and a gap left between the top end and the cavity wall.

[0015] Furthermore, in the isolation-power distribution unit, along the channel direction, grooves are provided on the base plate between adjacent metal pillars, and each groove connects the input channel to the upper or lower channel on the corresponding side.

[0016] Furthermore, in the isolation-power distribution unit, a BeO attenuator with a gradually changing structure is loaded at the end of the input channel, the beginning of the upper channel, and the beginning of the lower channel, respectively.

[0017] Furthermore, the cover plate is a rectangular metal plate with an array of grooves etched on it. The cover plate covers the top of the base plate, and each groove on the cover plate is directly opposite to each groove in the base plate.

[0018] Furthermore, the gradient structure is wedge-shaped.

[0019] Beneficial Effects: Although existing W-band filter-type power dividers have achieved a certain degree of integration of power distribution and spectrum shaping, significant shortcomings remain. First, the series or superimposed design of filtering and power division functions results in a complex overall device structure and large size, making it difficult to meet the miniaturization and high-density integration requirements of high-frequency systems. Second, existing structures rely on limited transmission zero control for out-of-band suppression, resulting in narrow bandwidth and insufficient suppression depth, making them susceptible to spurious interference. Furthermore, isolation branches or power-consuming components introduced to improve port isolation often cause additional insertion losses and disrupt the phase balance at the output, affecting signal quality and system stability. In addition, the complex coupling structure demands extremely high manufacturing precision and has poor process tolerance, leading to significant performance fluctuations during actual processing and packaging. In summary, existing W-band filter-type power dividers generally suffer from large size, weak suppression, poor isolation, and high manufacturing difficulty, necessitating innovative structural design to achieve a balance between miniaturization, high suppression, and high isolation performance.

[0020] The present invention discloses a compact W-band filter power divider with anti-phase output characteristics, which integrates a multi-stage filter network, a vertically coupled power distribution module and an absorption isolation mechanism. Through system optimization of the coupling path, resonant unit and output topology, it achieves the synergistic characteristics of equal amplitude power distribution, 180-degree output phase difference, deep out-of-band suppression and high isolation output, thus meeting the integration requirements of high-performance millimeter-wave subsystems.

[0021] Specifically, this invention is the first to deeply integrate multi-stage bandpass filtering, symmetrical power coupling distribution, and isolation mechanisms into a single, compact W-band power divider. By introducing a resonant unit in the main channel, a multi-zero filtering response is achieved, endowing the device with high spectral selectivity and broadband suppression capabilities. In the isolation-power distribution unit, a vertical coupling path is constructed, coupled with a highly symmetrical upper and lower channel layout, to achieve equal-amplitude power distribution and phase-consistent output within the passband while maintaining a compact structure. Simultaneously, a wedge-shaped BeO (beryllium oxide) absorption structure is innovatively introduced, which achieves the dissipation and absorption of reflected and stray signals through a gradually changing cross-section and symmetrical arrangement, significantly improving the inter-port isolation. The in-band isolation performance is better than 20 dB, solving the problems of poor isolation, severe out-of-band leakage, and large structural volume in traditional W-band power divider structures.

[0022] Furthermore, this structure employs an all-metal cavity design, possessing excellent thermal stability and vacuum compatibility, making it particularly suitable for power combining and signal distribution scenarios in high-power vacuum electronic devices. The introduced BeO wedge absorber not only exhibits good microwave loss characteristics, but its high thermal conductivity and vacuum adaptability also enable it to efficiently absorb parasitic energy and suppress mode reflections in a vacuum environment, meeting the engineering requirements of high-power millimeter-wave systems.

[0023] The isolation-power distribution unit has grooves loaded on the base plate between adjacent metal pillars to regulate the propagation characteristics of the master mode and suppress higher-order mode interference, thereby improving out-of-band stability and electromagnetic shielding performance.

[0024] The device adopts an all-metal integrated structure, which is compatible with LIGA, CNC or micro-milling technology. The structure is symmetrical and compact, which facilitates system integration and packaging. It is suitable for W-band communication, radar and imaging systems at the 94 GHz center frequency, and can be used as a front-end passive sub-module to realize signal selection, distribution and suppression. Attached Figure Description

[0025] Figure 1 This is a schematic diagram of the external structure of a compact W-band filter power divider with inverted output characteristics.

[0026] Figure 2 This is a schematic diagram of the yoz cross-section of a compact W-band filter power divider with inverted output characteristics;

[0027] Figure 3 This is a schematic diagram of the bandpass filter network of a power divider.

[0028] Figure 4 This is a schematic diagram of the base plate structure of the isolation-power distribution unit of the filter power divider;

[0029] Figure 5 This is a schematic diagram of the cover plate structure of the isolation-power distribution unit of the filter power divider;

[0030] Figure 6 A schematic cross-sectional view of the output coupling structure;

[0031] Figure 7 The diagram shows the yoz cross-sectional dimensions of a compact W-band filter power divider with inverted output characteristics, as illustrated in the embodiment.

[0032] Figure 8 This is a diagram showing the xoz cross-sectional dimensions of a compact W-band filter power divider with inverted output characteristics, as illustrated in the embodiment.

[0033] Figure 9 This is a diagram showing the xoy cross-sectional dimensions of the resonant unit of the bandpass filter network in the embodiment of the filter power divider;

[0034] Figure 10 The reflection coefficient S of the power divider filter in the example 11 and insertion loss S 21 Simulation experiment diagram;

[0035] Figure 11 The isolation parameter S of the power divider filter in the example is shown. 32 and reflection coefficient S 11 Simulation experiment diagram;

[0036] Figure 12 The simulation diagram of the phase difference at the output port of the filter power divider is shown in the example.

[0037] Figure 13 The following is a simulation diagram of the group delay of the filter power divider in the example embodiment;

[0038] Figure 14 The diagram shows the electric field vector distribution at the input port of the power divider filter in this embodiment.

[0039] Figure 15 The diagram shows the electric field vector distribution when the output port of the filter power divider is excited, as shown in the example. Detailed Implementation

[0040] The invention will now be further explained with reference to the accompanying drawings.

[0041] like Figure 1 , Figure 2 As shown, a compact W-band filter power divider with inverted output characteristics includes input port 1, output port 2, output port 3, bandpass filter network 4, isolation-power distribution unit 5, and output coupling structure 6. Standard WR10 waveguides are used at input port 1, output port 2, and output port 3.

[0042] like Figure 3As shown, the bandpass filter network 4 is an all-metal cavity structure, consisting of a central resonant unit 402 and symmetrical stepped impedance transformation sections 401 about both ends of the resonant unit 402. One side of the stepped impedance transformation section 401 is connected to the standard WR10 waveguide of the input port 1. This stepped impedance transformation section 401 achieves a broadband impedance transition from the standard WR10 waveguide port to the resonant unit 402 by progressively adjusting the waveguide cross-sectional dimensions, effectively reducing reflections and improving port matching performance. The resonant unit 402 consists of multiple sets of metal rectangular pillars arranged within the cavity. Each set of metal rectangular pillars consists of several metal rectangular pillars evenly spaced along the length of the cavity; each metal rectangular pillar is perpendicular to the length of the cavity; the bottom end of each metal rectangular pillar is connected to the cavity wall, and a gap is left between the top end and the cavity wall. This gap, as well as the gap between two adjacent metal rectangular pillars in the same set, is called a slot. One set of metal rectangular pillars is arranged along the axis of the cavity, and the other sets of metal rectangular pillars are symmetrically distributed on both sides of this set. There are gaps between each group of metal rectangular columns, and between the sides of the two outermost groups of metal rectangular columns and the cavity wall. These gaps are called slits.

[0043] The resonant unit 402 utilizes the aforementioned slit and slot structure to form a strong coupling channel with its main waveguide, achieving multi-stage bandpass filtering and multiple transmission zero generation, significantly improving out-of-band rejection and frequency selectivity. The stepped impedance transformation section 401 on the other side is connected to the isolation-power distribution unit 5. This stepped impedance transformation section 401 is used to achieve impedance matching from the resonant unit 402 to the isolation-power distribution unit 5. The two symmetrically arranged stepped impedance transformation sections 401 are structurally closely connected to the middle resonant unit 402, functionally forming two sides of the input matching network. Together, the two stepped impedance transformation sections 401 ensure good bidirectional coupling and low-reflection transmission between the bandpass filter network 4 and the remaining structures of the filter power divider.

[0044] The isolation-power distribution unit 5 is a cavity structure formed by a base plate and a cover plate. For example... Figure 4The base plate structure shown includes a central input channel 501 and symmetrically distributed upper and lower channels 502 and 503 on either side of the input channel 501. The starting end of the input channel 501 is connected to the end of the bandpass filter network 4, specifically to one end of the stepped impedance transformation section 401 on the right side of the bandpass filter network 4. The input channel 501 is separated from the upper and lower channels 502 and 503 by a metal partition 504, a series of evenly spaced metal pillars 505, and a metal partition 506, respectively, from the starting end to the end of the channel. The two rows of metal pillars 505 on either side of the input channel 501 form a vertical coupling path with the upper and lower channels 502 and 503. Along the channel direction, grooves 507 are provided on the base plate between adjacent metal pillars 505, with the grooves 507 and metal pillars 505 alternating sequentially. Each groove 507 bridges the input channel 501 with the corresponding upper or lower channel 502. To reduce reflections and improve isolation between channels, a BeO attenuator 508 with a gradient structure is loaded at the end of input channel 501, a BeO attenuator 509 with a gradient structure is loaded at the beginning of upper channel 502, and a BeO attenuator 510 with a gradient structure is also loaded at the beginning of lower channel 503. The ends of upper channel 502 and lower channel 503 are connected to the output coupling structure 6.

[0045] like Figure 5 As shown, the cover plate is a rectangular metal plate with an array of grooves 511 etched on its inner side. The cover plate is fitted onto the top of the base plate. Each groove 511 is directly opposite to a groove 507 in the base plate, forming a symmetrical electric field control structure to stabilize mode propagation and suppress higher-order mode excitation and parasitic coupling. The entire structure of the isolation-power distribution unit 5 is highly symmetrical and compactly integrated, suitable for millimeter-wave band processing technology and conversion implementation.

[0046] like Figure 6 As shown, the output coupling structure 6 adopts a symmetrical dual-channel waveguide form, consisting of a pair of standard WR10 waveguides 601 and 602 serving as output ports 2 and 3, and a pair of arc-shaped transition structures 603 and 604. Both arc-shaped transition structures 603 and 604 are 90° curved channel structures. The starting end of arc-shaped transition structure 603 is connected to the end of the upper channel 502 of the isolation-power distribution unit 5, and the end of arc-shaped transition structure 603 is connected to the standard WR10 waveguide 601. The starting end of arc-shaped transition structure 604 is connected to the end of the lower channel 503 of the isolation-power distribution unit 5, and the end of arc-shaped transition structure 604 is connected to the standard WR10 waveguide 602. In the arc-shaped transition structures 603 and 604, which serve as transition sections, directional rotation is introduced in the 90° curved waveguides, causing TE... 10During propagation in the curved waveguide, the direction of the spatial electric field is mirrored and flipped, eventually generating a stable 180-degree phase difference at the two output ports.

[0047] Furthermore, the arc-shaped transition structures 603 and 604 are used to achieve a smooth mode transition from the internal dual-path transmission channel of the isolation-power distribution unit 5 to the external output port. By optimizing the geometric curve profile of the arc-shaped transition structure, the reflection and radiation loss of W-band high-frequency signals at the bend can be effectively reduced, thereby reducing the transmission of in-band signals. While maintaining the same amplitude output, a stable 180° phase difference can be formed between output port 2 and output port 3, i.e., inverted output, which is suitable for differential excitation millimeter-wave systems.

[0048] The aforementioned W-band filter power divider integrates a bandpass filter network, an isolation-power distribution unit, and an output coupling structure, achieving high-selectivity spectrum control, equal-amplitude power distribution, and high-isolation output in a coordinated manner. In this embodiment, the resonant unit 402 has three sets of metal rectangular pillars. Under the excitation of the input signal, the signal enters the resonant unit 402 through the stepped impedance transformation section 401 at the input port 1 with good matching. When the working signal within the passband passes through, it will excite the electromagnetic resonance mode between the metal rectangular pillars loaded in the resonant unit 402, allowing the signal to pass through with low insertion loss, forming a bandpass response, and constituting three resonant points between the three sets of metal rectangular pillars in this embodiment; while signals outside the passband cannot meet the resonance condition and are strongly reflected or attenuated in the coupling region, forming multiple transmission zeros, thereby achieving deep out-of-band suppression.

[0049] The RF signal with good bandpass response is further transmitted to the input channel 501 of the isolation-power distribution unit 5. After passing through the periodic metal pillars 505 on both sides of the input channel 501, electromagnetic coupling between the channels is achieved. This allows the input signal energy to be efficiently and evenly distributed between the upper channel 502 and the lower channel 503 within the passband frequency range, realizing the power distribution function of the equal-amplitude coupling mode. During this process, due to the symmetry of the isolation-power distribution unit 5 structure, the two signals output from the upper channel 502 and the lower channel 503 have good amplitude balance. If interference signals are present due to imbalance or reflection, they will be dissipated or canceled by the BeO attenuators with a gradient structure at the ends of the upper channel 502, lower channel 503, and input channel 501, thereby significantly suppressing the re-injection of non-ideal coupled signals and improving the isolation between the upper channel 502 and the lower channel 503. Simultaneously, the groove array 507, by adjusting the local electric field distribution, can effectively constrain the propagation path of the master mode, avoiding parasitic mode excitation and electromagnetic leakage, further enhancing out-of-band suppression and system stability.

[0050] The RF signal with filtering and power distribution enters the output coupling structure 6. Although the geometry of the output coupling structure 6 is completely symmetrical, the directional rotation introduced by the bent waveguides in the two output channels causes the TE... 10 During the propagation of the master mode through the bend, the spatial electric field direction is mirrored and flipped. This, combined with the inherent odd-mode excitation characteristics in the coupling channel, ultimately produces a stable 180-degree phase difference at the two output ports. Output coupling structure 6 achieves a smooth mode transition from the internal dual-path transmission structure to the external output port, ultimately outputting the mode through output ports 2 and 3 with equal amplitude and inverse phase.

[0051] The W-band filter power divider of this invention is manufactured with an all-metal structure, possessing excellent impedance matching characteristics and high-frequency structural stability. It can be directly connected to standard rectangular waveguides or feed arrays, making it suitable for the output interface scenarios of highly integrated millimeter-wave subsystems.

[0052] This embodiment designs a compact W-band filter power divider with inverted output characteristics and a center frequency of 93.562 GHz, and verifies it through simulation after modeling using simulation software. The metal material is oxygen-free copper, and considering losses during actual processing, the conductivity is set to σ = 2.7 × 10⁻⁶. 7 The relative permittivity of the BeO attenuator is ε=6.5, and the loss tangent is δ=0.7.

[0053] like Figures 7 to 9 As shown, in the compact W-band filter power divider of this embodiment, the xoy cross-section of the cavity of the bandpass filter network 4 is rectangular, and the resonant unit 402 is provided with three sets of metal rectangular pillars; the BeO attenuator with a gradient structure adopts a wedge structure. As shown in the figure, the dimensional parameters of each structure are: Wb=1.27, FL1=1.50, FL2=0.75, FL3=0.50, FL4=1.00, FL5=0.50, Ft1=0.15, Ft2=0.15, AL=2.0, DL1=4.14, DL2=0.54, DL3=0.50, Dh1=1.84, R=2.27, Wa=2.54, Fw1=2.06, Fw2=1.96, ta=0.45, tb=0.15, tc=0.15, Dh2=3.5, Ht1=2.54, Ht2=0.58. The units of the dimensional parameters are mm.

[0054] like Figure 10 As shown, the reflection coefficient S obtained from this embodiment 11 and insertion loss S 21 As can be seen from the curve, the compact W-band filter power divider structure of this embodiment has an insertion loss S after removing the 3dB power distribution in the frequency range of 92.03-95.24GHz. 21Less than 0.92dB, reflection coefficient S 11 Less than -20dB, the 3-dB relative bandwidth of 91.08~96.50GHz is 5.78%. In the frequency bands below 80GHz and above 110GHz, S... 21 The rejection rate drops rapidly to below -60dB, demonstrating excellent out-of-band suppression. Out-of-band suppression is better than -20dB in the 98.8-129.1GHz range. Furthermore, three poles appear within the band at 92.1GHz, 93.6GHz, and 95GHz, while a transmission zero exists near 80GHz and 120GHz outside the band, exhibiting good out-of-band suppression.

[0055] like Figure 11 As shown, the reflection coefficient S obtained from this embodiment 11 And isolation coefficient S 32 It can be seen that the isolation bandwidth covers the passband and above, and the isolation is greater than 20dB in the frequency range of 91.72-95.46GHz, with an isolation bandwidth of 4%.

[0056] like Figure 12 As shown, the phase difference between output port 2 and output port 3 obtained in this embodiment shows that the two ports are 180 degrees out of phase, verifying that the device has inverted output characteristics.

[0057] like Figure 13 As shown, the group delay obtained from this embodiment can be seen that the group delay is less than 0.35ns in the 90-100GHz range, indicating the relative stability of signal transmission.

[0058] like Figure 14 As shown in the vector diagram of the electric field distribution when the input port 1 is excited, it can be seen that when the input port 1 is excited, the electric field vectors of the output port 2 and the output port 3 are opposite and have the same amplitude, which verifies the balance and anti-phase characteristics of the power distribution.

[0059] like Figure 15 As shown in the vector diagram of the electric field distribution when the input port 1 is excited by the signal obtained in this embodiment, it can be seen that when the output port 2 is excited by the signal, the electric field vector amplitude of the output port 3 is very small, exhibiting good isolation characteristics.

[0060] In summary, the simulation results fully demonstrate the technical advantages of this invention in key performance indicators such as structural design, phase control, isolation capability, and out-of-band suppression.

[0061] The above description is only a preferred embodiment of the present invention. It should be noted that for those skilled in the art, several improvements and modifications can be made without departing from the principle of the present invention, and these improvements and modifications should also be considered within the scope of protection of the present invention.

Claims

1. A compact W-band filter power divider with inverted output characteristics, characterized in that, include: One input port, two output ports, a bandpass filter network (4), an isolation-power distribution unit (5), and an output coupling structure (6); The bandpass filter network (4) is a cavity structure, including a middle resonant unit (402) and two stepped impedance transformation segments (401) symmetrically connected to both ends of the resonant unit (402); wherein the stepped impedance transformation segment (401) on the left is connected to the input port. The isolation-power distribution unit (5) includes a cavity structure formed by a base plate and a cover plate. The cavity structure is divided into a middle input channel (501) and an upper channel (502) and a lower channel (503) symmetrically distributed on the upper and lower sides of the input channel (501). The starting end of the input channel (501) is connected to the stepped impedance transformation section (401) on the right side of the bandpass filter network (4). Vertical coupling paths are respectively provided between the input channel (501) and the upper channel (502) and the lower channel (503). The output coupling structure (6) includes two symmetrical arc transition structures. The starting ends of the two arc transition structures are respectively connected to the ends of the upper channel (502) and the lower channel (503), and the ends of the two arc transition structures are respectively connected to the two output ports. The curved waveguides of the two arc transition structures are provided with directional rotation that causes the main mode to undergo a mirror flip of the spatial electric field direction during the propagation of the curved waveguide.

2. The compact W-band filter power divider with inverted output characteristics according to claim 1, characterized in that, The resonant unit (402) is composed of multiple sets of metal rectangular pillars arranged in the cavity. Each set of metal rectangular pillars is composed of several metal rectangular pillars evenly spaced along the length of the cavity. One set of metal rectangular pillars is arranged along the axis of the cavity, and the other sets of metal rectangular pillars are symmetrically distributed on both sides of the set.

3. The compact W-band filter power divider with inverted output characteristics according to claim 1, characterized in that, In the isolation-power distribution unit (5), the input channel (501) is separated from the upper channel (502) and the lower channel (503) by a first metal partition (504), a plurality of metal pillars (505) evenly spaced and a second metal partition (506) from the beginning to the end of the channel, respectively; wherein, the plurality of metal pillars (505) evenly spaced serve as the vertical coupling path.

4. The compact W-band filter power divider with inverted output characteristics according to claim 1, characterized in that, The input port and both output ports use standard WR10 waveguides.

5. The compact W-band filter power divider with inverted output characteristics according to claim 2, characterized in that, In the resonant unit (402), each metal rectangular column is arranged perpendicular to the length direction of the cavity. The bottom end of the metal rectangular column is connected to the cavity wall, and a gap is left between the top end and the cavity wall.

6. The compact W-band filter power divider with inverted output characteristics according to claim 3, characterized in that, In the isolation-power distribution unit (5), along the channel direction, a groove (507) is provided on the base plate between adjacent metal pillars (505), and each groove (507) is connected across the input channel (501) and the upper channel (502) or lower channel (503) on the corresponding side.

7. The compact W-band filter power divider with inverted output characteristics according to claim 3 or 6, characterized in that, In the isolation-power distribution unit (5), a BeO attenuator with a gradient structure is loaded at the terminal of the input channel (501), the starting end of the upper channel (502), and the starting end of the lower channel (503).

8. The compact W-band filter power divider with inverted output characteristics according to claim 6, characterized in that, The cover plate is a rectangular metal plate with an array of etched grooves. The cover plate covers the top of the base plate, and each groove on the cover plate is directly opposite to each groove in the base plate.

9. The compact W-band filter power divider with inverted output characteristics according to claim 7, characterized in that, The gradient structure is wedge-shaped.

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