Multi-antenna MIMO architecture synchronization method and device, program product and storage medium

Abstract

The invention provides a multi-antenna MIMO architecture synchronization method and device, a program product and a storage medium, and relates to the technical field of wireless communication. Receiving sampling signals through a plurality of receiving channels; performing down-sampling on each sampling signal to obtain a down-sampling signal; determining a plurality of cache regions to store each downsampling signal, and performing cross-correlation operation on each downsampling signal and a local synchronous time domain signal; when any receiving channel detects an effective peak value, determining the position of the effective peak value as a preliminary synchronization position; determining a corresponding search window range, and performing weighted stacking on the target cross-correlation results to obtain an overall correlation peak value; searching a maximum value in all the total correlation peak values, and determining a position corresponding to the maximum value as a final synchronization position; and calculating a frequency offset estimation value of each receiving channel according to each pilot signal, and carrying out weighted average on each frequency offset estimation value to obtain a final frequency offset estimation value. By adopting the method, the wireless frame synchronization precision can be improved.

Description

TECHNICAL FIELD

[0001] The present application relates to the technical field of wireless communication, and in particular to a multi-antenna MIMO architecture synchronization method, device, program product and storage medium. BACKGROUND

[0002] In a wireless communication system, the multiple-input multiple-output (MIMO) technology improves the data transmission rate and reliability of the system by using multiple transmitting antennas and receiving antennas. In order to ensure the normal operation of the MIMO system, the receiving end needs to accurately detect and synchronize the synchronization sequence in the wireless frame to achieve time synchronization.

[0003] In the prior art, for example, CN106603131A "Frame synchronization method for MIMO system" discloses a technical solution for determining the synchronization point by using the mode method. The method selects the position with the highest frequency of occurrence as the final synchronization point by counting the synchronization positions detected by each receiving channel.

[0004] However, the existing mode method has the following technical problems: when the multipath environment is too complex, the mode method often does not work well and cannot fully exert the performance advantages of multi-antenna joint anti-noise. Specifically, when the channel performance is poor, if the performance of each receiving channel cannot meet the peak detection requirement, the problem of missing detection of the synchronization signal will occur, resulting in a decrease in synchronization accuracy. SUMMARY

[0005] The present application provides a multi-antenna MIMO architecture synchronization method, device, program product and storage medium, which can improve the accuracy of synchronizing the wireless frame.

[0006] In a first aspect of the present application, a multi-antenna MIMO architecture synchronization method is provided, which specifically comprises: receiving a sampling signal through a plurality of receiving channels, the number of receiving channels being the product of the number of transmitting antennas and the number of receiving antennas; down-sampling each sampling signal to obtain a down-sampled signal; determining that a plurality of buffer areas store each down-sampled signal, the number of buffer areas being equal to the number of receiving channels; when all buffer areas have the down-sampled signal, performing cross-correlation operation on each down-sampled signal and a local synchronization time-domain signal to obtain a cross-correlation result on each receiving channel; when any receiving channel detects a valid peak value, determining the position of the valid peak value as a preliminary synchronization position, the valid peak value being a peak value that meets a preset condition in each cross-correlation result; According to the corresponding search window range determined according to each preliminary synchronization position, target cross-correlation results of each receiving channel marked as synchronization success within the search window range are weighted and superimposed to obtain a total correlation peak value corresponding to each search window range; A maximum value is searched in all total correlation peak values, and a position corresponding to the maximum value is determined as a final synchronization position; According to the final synchronization position, pilot signals of each receiving channel are extracted, frequency offset estimation values of each receiving channel are calculated according to each pilot signal, and weighted average is performed on each frequency offset estimation value to obtain a final frequency offset estimation value.

[0007] By adopting the technical scheme, the effective peak position detected by any receiving channel is taken as a preliminary synchronization position, a search window is established with the position as a center, cross-correlation results of all receiving channels within the window range are weighted and superimposed, and signal energy of multiple receiving paths in the MIMO system is fully utilized. This scheme not only overcomes the limitation of determining the synchronization position by relying on the statistical mode in the prior art, but also realizes joint enhancement of multi-antenna signal energy when the channel condition is poor and the performance of a single channel is insufficient. In addition, the frequency offset estimation accuracy is further improved by performing weighted average on the frequency offset estimation values of each receiving channel. The scheme significantly improves the synchronization performance and reliability of the MIMO system in a complex multipath environment, provides strong support for high-quality wireless communication, and improves the synchronization wireless frame precision of the entire MIMO system in a complex environment.

[0008] Optionally, the cross-correlation operation of the plurality of down-sampling signals and the local synchronization time-domain signal to obtain the cross-correlation result on each receiving antenna comprises: The cross-correlation operation of the plurality of down-sampling signals and the local synchronization time-domain signal according to the first formula to obtain the cross-correlation result on each receiving antenna; The first formula is: wherein, SEQ(n) p is the cross-correlation result of the pth receiving channel at sampling time n, n is the sampling time, p is the index of the receiving channel, M is the length of the local synchronization sequence, m is the position index in the local synchronization sequence, S Q (Qm+n) is the down-sampling signal of the pth receiving channel at time Qm+n, Q is a sampling interval parameter, h * (m) is the conjugate of the local synchronization time-domain signal, N is the search range, M ant is the total number of receiving channels.

[0009] By adopting the above technical scheme, the mutual correlation operation formula is adopted, and the application realizes accurate mathematical processing of each received channel signal. The formula introduces a sampling interval parameter Q for down-sampling processing, effectively reduces the calculation complexity, and improves the detection sensitivity of the mutual correlation peak value through sequence conjugate operation. The formula considers the limitation of the search range N, avoids unnecessary calculation overhead, ensures the synchronization performance, and optimizes the system resource utilization. The design of the mathematical model enables the system to realize reliable peak value detection in a complex multipath environment, and lays a solid foundation for subsequent multi-channel joint processing.

[0010] Optionally, the searching for the peak value of each mutual correlation result, and determining the peak value meeting the preset condition as an effective peak value, comprises: determining a peak value detection parameter, the peak value detection parameter comprising an absolute threshold and a relative threshold; searching for a maximum value of each mutual correlation result in a preset time range to obtain a candidate peak value and a position of the candidate peak value; when the candidate peak value is greater than the absolute threshold, and a ratio of the candidate peak value to an average value of each candidate peak value is greater than the relative threshold, determining the candidate peak value as an effective peak value.

[0011] By adopting the above technical scheme, the setting of the absolute threshold ensures that the detected peak value has sufficient signal strength, and effectively suppresses noise interference; the relative threshold further improves the robustness of peak value detection by comparing the ratio of the candidate peak value to the average value, effectively avoiding false peak value misjudgment. This double-threshold decision method not only ensures the accuracy of synchronization detection, but also improves the adaptability of the system under different channel conditions, and provides a reliable preliminary synchronization position for subsequent multi-channel joint processing.

[0012] Optionally, after determining the candidate peak value as an effective peak value, the method further comprises: calculating an offset between the position of the effective peak value and a final synchronization position obtained from a previous radio frame time; when the offset is less than a preset offset threshold, confirming that the position of the effective peak value is valid, and recording the position of the effective peak value in the preset time range.

[0013] By adopting the technical scheme, the judgment mechanism of the inter-frame position offset is introduced to further verify the detected effective peak position. Since the synchronization positions of adjacent wireless frames have the time continuity feature, by comparing the effective peak position detected in the current frame with the final synchronization position of the last frame and setting a reasonable preset offset threshold, the abnormal peak caused by the burst interference or the severe channel fluctuation can be effectively identified and eliminated. The double verification mechanism based on the time continuity not only improves the reliability of the synchronization position detection, but also realizes the real-time tracking of the channel change, thereby ensuring the stable operation of the MIMO system in the dynamic channel environment.

[0014] Optionally, the search window range is determined according to the preliminary synchronization position, the target cross-correlation results of the receiving channels marked as synchronization success within the search window range are weighted and superimposed to obtain an overall correlation peak, and the method comprises the following steps: A search window range with a preset length is set with the preliminary synchronization position as the center; The receiving channel detecting the effective peak is marked as synchronization success; The corresponding target cross-correlation results of the receiving channels marked as synchronization success within the search window range are extracted; and the target cross-correlation results are weighted and superimposed according to a preset weight coefficient to obtain an overall correlation peak.

[0015] By adopting the technical scheme, the preset search window range effectively limits the region of the correlation calculation, and reduces the calculation complexity; the synchronization success marking mechanism can accurately identify the receiving channel with reliable synchronization characteristics, and avoids the influence of the interference channel on the system performance. Further, the cross-correlation results of the receiving channels marked as synchronization success are weighted and superimposed, the spatial diversity characteristics of the multiple antennas are fully utilized, the anti-noise capability of the system is improved, the detectability of the correlation peak is significantly enhanced, and the system can obtain a more accurate synchronization time in the complex multipath environment.

[0016] Optionally, the pilot signals of the receiving channels are extracted according to the final synchronization position, the frequency offset estimation values of the channels are calculated and weighted and averaged to obtain a final frequency offset estimation value, and the method comprises the following steps: The corresponding pilot signals are extracted from the signals of the receiving channels according to the final synchronization position; The frequency offset estimation values of the receiving channels are obtained by performing frequency offset estimation calculation on the pilot signal segments; The synchronization success flag bits of the receiving channels are obtained, the frequency offset estimation values of the receiving channels are multiplied by the corresponding synchronization success flag bits, and then the multiplication results are accumulated and summed to obtain an accumulation and summation result; The accumulated summation result is divided by the sum of all the synchronization success flag bits to obtain a final frequency offset estimation value.

[0017] By adopting the technical scheme, firstly, the pilot signals of each receiving channel are extracted by using the accurate final synchronization position, and the reliability of the basic data of the frequency offset estimation is ensured; by taking the synchronization success flag bit as a weight coefficient, the selective weighting of the frequency offset estimation values of different receiving channels is achieved, and the adverse influence of the channel with poor quality on the frequency offset estimation is effectively inhibited. Meanwhile, by adopting the ratio operation of the accumulated summation and the sum of the flag bits, the spatial diversity advantage of the multi-antenna system is fully utilized, and the adaptive normalization processing of the frequency offset estimation value is realized, and the frequency offset estimation precision and reliability of the system in the complex channel environment are significantly improved.

[0018] Optionally, the downsampling of each of the sampling signals to obtain a down-sampled signal comprises: performing low-pass filtering processing on each of the sampling signals to filter out signals outside the frequency band of the local synchronization signal, and the cut-off frequency of the low-pass filter is set as the bandwidth of the local synchronization signal; setting a downsampling multiple, and performing downsampling processing on the low-pass filtered signal according to the downsampling multiple, so that the signal rate of the down-sampled signal is a preset multiple of the sampling multiple of the local synchronization time domain signal, to obtain a down-sampled signal.

[0019] By adopting the technical scheme, firstly, by accurately setting the cut-off frequency of the low-pass filter as the bandwidth of the local synchronization signal, the effective inhibition of the out-of-band noise and interference is realized, and the signal-to-noise ratio is improved; secondly, by adopting the adjustable downsampling multiple, the signal rate of the down-sampled signal is kept in a reasonable multiple relationship with the local synchronization signal, and the data processing amount is significantly reduced on the premise of ensuring the synchronization accuracy. This preprocessing mechanism not only reduces the computational burden of the system and improves the processing efficiency, but also enhances the anti-interference ability of the system through the joint action of filtering and downsampling, and provides a more reliable signal basis for the subsequent cross-correlation operation.

[0020] In a second aspect, the present application provides a multi-antenna MIMO architecture synchronization device, comprising: one or more processors and a memory; the memory is coupled with the one or more processors, the memory is used to store computer program code, the computer program code comprises computer instructions, and the one or more processors invoke the computer instructions to enable the multi-antenna MIMO architecture synchronization device to execute the method as described in the first aspect and any possible implementation manner of the first aspect.

[0021] In a third aspect, the present application provides a computer program product comprising instructions which, when the computer program product is executed on a multi-antenna MIMO architecture synchronization device, cause the multi-antenna MIMO architecture synchronization device to perform the method as described in the first aspect and any possible implementation of the first aspect.

[0022] In a fourth aspect, the present application provides a computer-readable storage medium comprising instructions which, when executed on a multi-antenna MIMO architecture synchronization device, cause the multi-antenna MIMO architecture synchronization device to perform the method as described in the first aspect and any possible implementation of the first aspect. BRIEF DESCRIPTION OF DRAWINGS

[0023] Figure 1 is a schematic diagram of a multi-antenna MIMO architecture synchronization system provided by an embodiment of the present application; Figure 2 is a schematic diagram of a multi-antenna MIMO architecture synchronization method provided by an embodiment of the present application; Figure 3 is a flowchart of a MIMO synchronization processing process of an exemplary dual-antenna provided by an embodiment of the present application; Figure 4 is a schematic diagram of an exemplary hardware structure of a multi-antenna MIMO architecture synchronization device provided by an embodiment of the present application. DETAILED DESCRIPTION

[0024] In order for those skilled in the art to better understand the technical solutions in the specification, the technical solutions in the specification will be clearly and completely described below in conjunction with the drawings in the embodiments of the specification. Obviously, the described embodiments are only some of the embodiments of the present application, not all the embodiments.

[0025] In the description of the embodiments of the present application, the words such as “for example” or “for instance” are used to represent an example, illustration or description. Any embodiment or design scheme described as “for example” or “for instance” in the embodiments of the present application should not be interpreted as more preferred or more advantageous than other embodiments or design schemes. Rather, the words such as “for example” or “for instance” are intended to present the relevant concept in a specific manner.

[0026] In the description of the embodiments of the present application, the term "a plurality of" means two or more. For example, a plurality of systems means two or more systems, and a plurality of screen terminals means two or more screen terminals. In addition, the terms "first", "second", etc. are used only for the purpose of description and should not be understood as indicating or implying relative importance or implying the indicated technical features. Therefore, the features defined with "first", "second", etc. can explicitly or implicitly include one or more of the features. The terms "include", "contain", "have" and their variants mean "include but are not limited to", unless otherwise specifically emphasized.

[0027] Figure 1 An architecture schematic of a multi-antenna MIMO architecture synchronization system is shown.

[0028] As shown in Figure 1 , the system architecture can include a receiving antenna array 011, a network 012 to provide a communication link between the receiving antenna array 011 and an electronic device 013. The network 012 can include various connection types, such as radio frequency transmission lines, coaxial cables, or optical fiber communications, etc.

[0029] The electronic device 013 can receive signal data collected by the receiving antenna array 011 through the network 012, and process and analyze the signal data to determine the signal synchronization position. Various signal processing applications can be configured on the electronic device 013, such as cross-correlation operation applications, peak search applications, and frequency offset estimation value calculation applications, etc.

[0030] The receiving antenna array 011 is hardware, which can be various types of antennas with signal receiving functions, including but not limited to spatially distributed receiving antenna elements such as dipole antennas, microstrip antennas, and helical antennas, etc.

[0031] The electronic device 013 can be a processing device that provides various angle measurement services, such as a server that processes and analyzes signals from the receiving antenna array 011. The server can perform cross-correlation operations, down-sampling processing, peak search, and frequency offset estimation value calculation on the received signals, and can perform output of the processing results.

[0032] It should be noted that the server can be hardware or software. When the server is hardware, it can be implemented as a distributed server cluster composed of multiple servers, or as a single server. When the server is software, it can be implemented as multiple software or software modules (such as multiple software or software modules for providing distributed services), or as a single software or software module. Herein, no specific limitation is made.

[0033] It should be understood that Figure 1The number of receiving antenna arrays 011, networks 012 and electronic devices 013 in the figure is only illustrative. According to the implementation needs, there can be any number of receiving antenna arrays 011, networks 012 and electronic devices 013. In particular, in the case where the target data does not need to be acquired from a remote place, the above-mentioned system architecture can not include the network 012, but only include the receiving antenna array 011 or the electronic device 013.

[0034] Next, taking the electronic device side as an example, a multi-antenna MIMO architecture synchronization method provided by the present application is described.

[0035] The present application provides a multi-antenna MIMO architecture synchronization method, referring to Figure 2 Figure 2 is a flowchart of a multi-antenna MIMO architecture synchronization method provided by an embodiment of the present application, including steps S101 to S108, which are as follows: S101: receiving a sampling signal through multiple receiving channels, the number of receiving channels being the product of the number of transmitting antennas and the number of receiving antennas.

[0036] In the present embodiment, the receiving channel refers to the logical representation of a specific wireless path through which a signal propagates from a single transmitting antenna to a single receiving antenna, which carries the channel characteristics such as amplitude, phase and time delay of the specific wireless path. In a communication electronic device configured with multiple transmitting antennas and multiple receiving antennas (i.e. MIMO), theoretically, there is an independent propagation path between each transmitting antenna and each receiving antenna, therefore, the total number of receiving channels is the product of the number of transmitting antennas and the number of receiving antennas. The sampling signal represents the digital signal sequence obtained after the continuous analog signal captured by the receiving antenna is sampled and quantized at discrete time points by an analog-to-digital converter (ADC), which is the basis for all subsequent digital signal processing.

[0037] ​Specifically, in a multi-antenna MIMO communication scenario, signals are simultaneously sent out by multiple transmitting antennas, propagate through complex spatial channels, and are captured by multiple receiving antennas at the receiving end. The signal received by each receiving antenna is actually a mixed signal formed by superimposing the signals sent out by all transmitting antennas after propagating through different propagation paths. At the receiving end, the analog signal received by each antenna is independently processed through a complete radio frequency front-end processing link, including low-noise amplification, filtering, frequency down-conversion, and the like, to convert the high-frequency radio frequency signal into a baseband or intermediate frequency analog signal. Subsequently, these parallel multiple analog signals are sent into respective analog-to-digital converters (ADCs) and sampled at a sampling rate set by the electronic device, thereby generating multiple parallel discrete digital sampling signal sequences. This step defines the input dimension of the electronic device, i.e., determines that the subsequent processing is not only the number of physical receiving antennas, but also the total number of logical receiving channels determined by the product of the number of transmitting antennas and the number of receiving antennas, thereby laying a data foundation for subsequent distinguishing and utilizing the spatial channels for synchronous processing.

[0038] S102: Down-sampling each sampling signal to obtain a down-sampled signal.

[0039] In the embodiments of the present application, down-sampling represents a technical processing procedure for reducing the sampling rate of a digital signal, and the core purpose is to reduce the data amount of the signal without losing key information, thereby reducing the computational complexity and storage overhead of subsequent processing.

[0040] Specifically, the cut-off frequency of the digital low-pass filter of each sampling signal is set. The cut-off frequency is set as the bandwidth occupied by the local synchronization signal. This has two purposes: one is to resist aliasing, i.e., to filter out all high-frequency noise and interference components that may be folded back into the signal frequency band due to the reduction of the sampling rate in advance before subsequent down-sampling, to ensure signal quality; the other is to improve the signal-to-noise ratio, by retaining only the useful frequency band related to the synchronization signal, effectively suppressing out-of-band noise, and making the synchronization signal feature more prominent. After filtering, down-sampling processing is performed. The electronic device sets a predetermined down-sampling multiple M, and then extracts every M sampling points to retain only 1. The selection of the down-sampling multiple is not arbitrary, but is to ensure that the final down-sampled signal has a data rate that is a preset multiple of the sampling rate of the local synchronization time-domain signal (usually a pre-existing reference signal). This matching or integral multiple relationship in rate can simplify the complexity of subsequent cross-correlation operations. Through filtering and down-sampling, multiple down-sampled signals with reduced data amounts are finally output, thereby laying a good foundation for subsequent fast and accurate synchronization detection.

[0041] On the basis of the above-mentioned embodiments, as an optional embodiment, S102: the step of down-sampling each sampling signal to obtain a down-sampled signal can specifically include the following steps: S701: performing low-pass filtering processing on each sampling signal to filter out signals outside the frequency band of the local synchronization signal, and the cut-off frequency of the low-pass filter is set to the bandwidth of the local synchronization signal.

[0042] In the embodiments of the present application, the low-pass filtering processing represents a signal processing mode that only allows components lower than a certain specific frequency (i.e., the cut-off frequency) in the signal to pass through, while significantly attenuating or filtering out components higher than the frequency.

[0043] Specifically, the sampling signals obtained from each receiving channel are processed independently and in parallel. Each sampling signal not only contains the synchronization signal to be detected, but also mixes channel noise, adjacent frequency interference from other wireless electronic devices, and out-of-band spurious signals and other unwanted components. In order to accurately extract the synchronization signal and improve the synchronization signal detection performance, the electronic device applies a digital low-pass filter to each signal. The key of this step lies in the parameter setting of the filter: the cut-off frequency of the digital low-pass filter is accurately set to be equal to the bandwidth of the locally stored synchronization signal. This setting ensures that the passband formed by the filter can perfectly cover and retain the complete synchronization signal spectrum, while effectively filtering out all high-frequency noise and interference signals outside the synchronization signal frequency band. Not only does it improve the signal-to-noise ratio of the signal, but it is also an essential pre-processing step for the subsequent down-sampling step, which can effectively prevent the spectral aliasing distortion problem that may occur due to the reduction of the sampling rate, thereby ensuring the accuracy and reliability of the entire synchronization process.

[0044] S702: setting a down-sampling multiple, and performing down-sampling processing on the low-pass filtered signal according to the down-sampling multiple, so that the signal rate of the down-sampled signal is a preset multiple of the sampling multiple of the local synchronization time domain signal, to obtain a down-sampled signal.

[0045] In the embodiments of the present application, the down-sampling multiple is a certain integer value, which is used to represent the number of original sampling points that need to be skipped to retain one sampling point when performing decimation down-sampling on the signal, and it directly determines the proportion of the reduction of the sampling rate.

[0046] Specifically, first, the electronic device needs to set the down-sampling multiple M according to a certain target. The target is that the signal rate output after the down-sampling processing is exactly equal to K times of the sampling rate of the local synchronous time-domain signal (K is a preset multiple). Therefore, the calculation method of the down-sampling multiple M is: M=(sampling rate of the low-pass filtered signal) / (sampling rate of the local synchronous time-domain signal* K). After the integer multiple M is calculated, the electronic device performs a down-sampling operation on the signal sequence filtered by the low-pass filter: for the input signal sequence, starting from the first point, every M sampling points are selected to be reserved, and the intermediate M-1 points are discarded. This process continues to traverse the entire signal sequence, and finally generates a new down-sampled signal with a length of about 1 / M of the original sequence. Through such controlled down-sampling, not only the data volume is compressed, but more importantly, the processed received signal and the local reference signal form an integer or preset multiple relationship in the sampling rate. This simplifies the algorithm complexity of subsequent cross-correlation peak searching, without the need for complex dynamic interpolation alignment, thereby improving the speed and efficiency of synchronization detection.

[0047] S103: Determine that a plurality of cache areas store respective down-sampled signals, and the number of cache areas is equal to the number of receiving channels.

[0048] In the embodiments of the present application, the cache area represents a specific area for temporarily storing data in the memory (such as RAM) of the electronic device, and its function is to temporarily store data and rate match between different stages of data processing.

[0049] Specifically, the electronic device first dynamically or statically allocates a corresponding number of independent cache areas in the memory according to the number of receiving channels currently configured or in an active state. For example, if the electronic device is configured with N receiving channels, the processing core will open up N independent cache spaces (Buffer 1, Buffer 2, …, Buffer N) of the same size. Then, the electronic device establishes a strict one-to-one correspondence: the down-sampled signal stream from the first receiving channel is stored in the first cache area; the signal stream from the second receiving channel is stored in the second cache area; and so on, the signal of the nth channel is only written into the nth cache area.

[0050] S104: When all cache areas have down-sampled signals, perform cross-correlation operation on the respective down-sampled signals and the local synchronous time-domain signal to obtain cross-correlation results on each receiving antenna.

[0051] In the embodiments of the present application, the cross-correlation operation represents a mathematical method for measuring the similarity of two signals (sequences) at different relative time offsets.

[0052] Specifically, the electronic device monitors the status of all N buffer areas in real time, and only when it is confirmed that each buffer area has received and stored the down-sampled signal data block from the corresponding receiving channel, the cross-correlation operation step is started. This mechanism ensures that all channels are synchronized in the same time window. After the operation starts, the electronic device will perform cross-correlation calculation on each receiving channel (from p = 1 to M_ant) according to the first formula, and obtain the cross-correlation result of each receiving antenna; The first formula is: Wherein, SEQ(n) p is the cross-correlation result of the pth receiving channel at sampling time n, n is the sampling time, p is the index of the receiving channel, M is the length of the local synchronization sequence, m is the position index in the local synchronization sequence, S Q (Qm+n) is the down-sampled signal of the pth receiving channel at time Qm+n, Q is the sampling interval parameter, h * (m) is the conjugate of the local synchronization time domain signal, N is the search range, M ant is the total number of receiving channels.

[0053] For the pth channel, the down-sampled signal S Q in the buffer area is taken as input. The calculation process is a sliding window summation: the conjugate sequence h * (m) of the local synchronization time domain signal with a length of M is taken as a matching template and is slid on the down-sampled signal S Q . Each step of the sliding is defined by the sampling time index n, and n ranges from 1 to N, defining the total search window size. At each sliding position n, the summation term ∑ in the formula calculates the sum of point-by-point products between the template h * (m) and the segment S Q of S Q (Qm+n) starting from n with a length of M and a sampling interval of Q. The square of the absolute value of this sum, i.e. SEQ(n) p , is the cross-correlation energy value of the pth channel at time offset n. After traversing all values of n, each channel p generates a sequence consisting of N cross-correlation values. M ant independent cross-correlation result sequences are obtained, each of which depicts the possible existence position and matching strength of the local synchronization signal in the corresponding receiving antenna signal.

[0054] The significance of constructing this formula structure is that: first, S QThe index structure of the term (Qm+n) is the key to efficient computation. It is not simply a continuous window cut on the down-sampled signal, but through the combination of sampling interval parameter Q and sliding index n, it realizes a step-sampling style window cutting. It can directly match two signals with slightly different sampling rates in one operation, avoiding additional interpolation or resampling preprocessing before cross-correlation operation, saving computing resources and processing delay. Then, the cut signal samples S Q The conjugate h * (m) multiplication, which is the core of complex correlation operation, has the significance that when the segment of the input signal matches the local signal, the phase of the multiplication result will be canceled, so that the energy is in-phase superimposed on the real axis, thus maximizing the accumulation value. The subsequent ∑ accumulation operation integrates the matching results within the entire window length M, so that the energy of the signal part is coherently accumulated, while the energy of the noise part is canceled due to its randomness in the accumulation process, thus significantly improving the signal-to-noise ratio of the signal in the noise background. Finally, the modulus square |...|2 of the accumulated complex result is taken, which has the significance of converting the complex result containing phase information into a real number representing only the signal energy. This not only simplifies the subsequent decision-making process (only need to find the maximum value), but also the square operation will further enhance the contrast of peak and sidelobe, making the correlation peak more sharp and prominent, improving the accuracy and reliability of detection.

[0055] S105: When any receiving channel detects a valid peak, the position of the valid peak is determined as the preliminary synchronization position, and the valid peak refers to the peak in each cross-correlation result that meets the preset condition.

[0056] Specifically, the electronic device first determines the absolute threshold and the relative threshold required for peak detection according to a preset configuration or channel environment evaluation. Then, the electronic device enters a search phase, traverses the cross-correlation result sequence of each receiving channel in the current processing wireless frame time window, finds and records the maximum value in the respective sequence as a candidate peak value, and records the position (sampling time n) corresponding to the maximum value as a candidate peak position. After obtaining the candidate peak values of all channels, the electronic device starts to determine the effectiveness of the candidate peak values one by one: first, the candidate peak value of a certain channel is compared with the absolute threshold, and only when the size of the candidate peak value is greater than the absolute threshold, it is preliminarily determined that it is likely to be a real signal, otherwise it is directly determined as invalid. Then, for the candidate peak value that passes the absolute threshold test, the electronic device calculates the arithmetic mean of all channel candidate peak values, and divides the candidate peak value by the mean to obtain a ratio. Only when the ratio is also greater than the preset relative threshold, the candidate peak value is finally confirmed as a valid peak value. Once an effective peak value that meets both conditions is detected on any receiving channel, the electronic device immediately determines the position of the effective peak value as a preliminary synchronization position, and can end the peak search in this round, thereby completing the preliminary synchronization.

[0057] On the basis of the above embodiment, as an optional embodiment, S105: the step of determining that the peak value is a peak value meeting a preset condition in each cross-correlation result can specifically include the following steps: S301: determining a peak detection parameter, the peak detection parameter including an absolute threshold and a relative threshold.

[0058] In the embodiment of the application, the absolute threshold represents a preset fixed energy threshold, which sets a minimum standard for the energy of the effective signal peak, and is mainly used to filter out the background noise and irrelevant signal interference that universally exist in the environment. The relative threshold represents a dynamic proportional threshold, which is not a fixed value but a ratio, and is used to measure the prominence of a candidate peak value relative to the average level of other channel candidate peak values.

[0059] Specifically, the determination of the absolute threshold is usually based on the prior knowledge of the electronic device and the evaluation of the communication environment. The core goal is to set a hard access threshold. The determination of the relative threshold is more based on the trade-off of the detection performance (such as the false alarm rate and the false alarm rate) of the electronic device, which is set to a coefficient greater than 1 (for example, 1.5 or 2). The selection of this value means that a peak value must be significantly higher than the peak value level on all antenna channels by a certain multiple to be considered valid. Finally, the absolute threshold representing the minimum energy requirement and the relative threshold representing the prominence requirement are obtained.

[0060] S302: search the maximum value of each cross-correlation result in a preset time range to obtain a candidate peak value and a position of the candidate peak value.

[0061] In the embodiments of the present application, the candidate peak value refers to an energy maximum value found in a specified time range (i.e., the preset time range) in the cross-correlation result sequence of a single receiving channel, which is regarded as the most likely synchronization point of the channel, but its effectiveness needs to be verified in subsequent steps.

[0062] Specifically, for each receiving channel, the electronic device performs a complete traversal scan on the cross-correlation result sequence of the receiving channel within the index range defined by the preset time range. During the scan process, the electronic device compares the current traversed value with the maximum value stored in a temporary variable in real time, and if the current value is larger, the temporary variable is updated and the position index of the current value is recorded. When the entire wireless frame time window is traversed, the final value stored in the temporary variable is the candidate peak value of the receiving channel, and the recorded position index is the position of the corresponding candidate peak value. Since the electronic device has multiple receiving channels (for example, multiple antenna reception), this operation is independently performed on each receiving channel, and finally a set of candidate peak values and positions are obtained.

[0063] S303: when the candidate peak value is greater than an absolute threshold and the ratio of the candidate peak value to the average value of the candidate peak values is greater than a relative threshold, the candidate peak value is determined as a valid peak value.

[0064] Specifically, the electronic device aggregates the candidate peak energy values reported by all receiving channels, adds them all together and divides by the total number of receiving channels (Mant), thereby calculating the average value of the candidate peak values. Then, the electronic device independently performs a double-threshold decision logic on each candidate peak value. For the candidate peak value of a particular channel, the electronic device performs two parallel judgments: first, whether the energy value of the candidate peak value is greater than a preset absolute threshold; second, whether the ratio of the energy value of the candidate peak value to the average value of the candidate peak values just calculated is greater than a preset relative threshold. Only when a candidate peak value satisfies both conditions can it be determined as a valid peak value. Any candidate peak value that fails to satisfy both conditions will be regarded as invalid and discarded.

[0065] On the basis of the above embodiments, as an optional embodiment, after the step of S303: determining the candidate peak value as a valid peak value, the step of verifying the position of the valid peak value is further included, which can specifically include the following steps: S401: calculate the offset between the position of the valid peak value and the final synchronization position obtained in the last wireless frame time.

[0066] In the embodiment of the present application, the offset refers to the difference between the valid synchronization position found in the current frame and the final synchronization position determined in the previous wireless frame in the time axis, which is used to represent the drift degree of the synchronization point between the continuous wireless frames and is a key indicator for measuring the synchronization stability.

[0067] Specifically, for any valid peak, the electronic device first reads the historical data of the final synchronization position obtained in the previous wireless frame from its internal storage unit. Then, a subtraction operation is performed to subtract the index of the final synchronization position of the previous frame from the index of the current valid peak. The result of the subtraction operation is defined as the offset of the valid peak. This calculation process independently calculates a corresponding offset value for each valid peak that passes the screening in S303. The offset value directly reflects the moving distance of the synchronization position between two frames, and its size will be used in the subsequent steps to determine whether the valid peak found is invalid due to excessive offset, thereby further enhancing the reliability and continuity of the synchronization positioning.

[0068] S402: When the offset is less than the preset offset threshold, the position of the valid peak is confirmed to be valid, and the position of the valid peak in the preset time range is recorded.

[0069] In the embodiment of the present application, the preset offset threshold refers to a value preset by the electronic device, which is used to represent the maximum allowable drift range of the synchronization position between the continuous two wireless frames that the electronic device can tolerate.

[0070] Specifically, the electronic device takes the offset corresponding to each valid peak and compares the offset with the preset offset threshold. If the offset of a valid peak is less than the preset threshold value, it indicates that the position of the peak changes gently compared with the synchronization reference point of the previous frame and is within a reasonable and predictable drift range. The electronic device therefore confirms that the position of the valid peak is valid and immediately records the time index of the position as a high-quality candidate synchronization point for subsequent steps. Conversely, if the calculated offset is equal to or greater than the preset offset threshold, the electronic device determines that the position of the valid peak has jumped and is likely to be caused by noise or serious channel fading, so even if it passes the previous energy detection, it is determined to be invalid due to its lack of continuity and stability, and its position information is discarded and not recorded.

[0071] S106: According to the corresponding search window range determined by each preliminary synchronization position, the target cross-correlation results of each receiving channel marked as synchronization success within the search window range are weighted and superimposed to obtain the overall correlation peak corresponding to each search window range.

[0072] In the embodiments of the present application, the overall correlation peak represents a synchronization signal peak obtained through multi-channel information fusion. The overall correlation peak is not a raw detection result from a single receiving channel, but a final synthesized peak obtained through weighted combination of correlation results of all receiving channels determined to be synchronized successfully within a search window range.

[0073] Specifically, first, the electronic device takes each preliminary synchronization position obtained in the previous step as a reference point, and extends a preset length in both forward and backward directions on the time axis, thereby defining an independent search window range.

[0074] Next, for the search window determined by a certain valid peak, the electronic device finds that the receiving channel of the valid peak is marked as synchronized successfully. Then, the electronic device extracts the data segment of the target cross-correlation result corresponding to the receiving channel within the time period of the search window range for each receiving channel marked as synchronized successfully. This is equivalent to slicing the original correlation result of each channel, and only keeping the part aligned with the current window.

[0075] Finally, the electronic device performs weighted superposition operation on the extracted channel data segments. At each sampling point position within the search window, the electronic device multiplies the target cross-correlation result value of each channel at the position by the preset weight coefficient (for example, the weight can be proportional to the signal-to-noise ratio of the channel) of the channel, and then adds all the weighted values. After performing the operation on all sampling points in the window, a new overall correlation curve fused with multi-channel information is generated. The peak point on the overall correlation curve is the overall correlation peak corresponding to the search window range. The process is independently performed for each search window defined by the preliminary synchronization position, and finally the number of overall correlation peaks equal to the number of windows is output.

[0076] On the basis of the above embodiments, as an optional embodiment, S106: according to the preliminary synchronization position, determine the corresponding search window range, and perform weighted superposition on the target cross-correlation results of the receiving channels marked as synchronized successfully within the search window range, to obtain the overall correlation peak corresponding to each search window range. The step can specifically include the following step: S501: set the search window range with a preset length centered on the preliminary synchronization position.

[0077] In the embodiments of the present application, the search window range refers to a local interval defined on the time axis with the preliminary determined synchronization point as the center, for fine search and data fusion.

[0078] Specifically, first, the electronic device will obtain the specific index value of the preliminary synchronization position in the time series, which will be used as the center point of the newly generated window. Then, the electronic device will read a fixed value of preset length from its configuration parameters. This length value determines the width of the search window, which is usually pre-set according to the evaluation of channel delay spread, clock frequency offset and other factors when the electronic device is designed. Finally, the electronic device performs a simple calculation: taking the index of the preliminary synchronization position as the center, extending half of the preset length to the left (time advance) and right (time lag), thereby obtaining the start position and end position of the search window. For example, if the preliminary synchronization position is at the 1000th sampling point and the preset length is 200 sampling points, the generated search window range is from the 900th sampling point to the 1100th sampling point.

[0079] S502: Mark the receiving channel where the valid peak is detected as synchronization success.

[0080] Specifically, when the electronic device detects a valid peak on any receiving channel and defines a search window range according to the valid peak, the electronic device will immediately expand the processing range to all physically available receiving channels. The electronic device will traverse each receiving channel in the electronic device, and mark the receiving channel where the valid peak is detected as synchronization success.

[0081] S503: Extract the target cross-correlation result corresponding to the search window range of each receiving channel marked as synchronization success.

[0082] In the embodiments of the present application, the target cross-correlation result represents a data segment extracted from the complete cross-correlation calculation result of a single receiving channel according to the search window range. It is not the entire channel cross-correlation curve, but only the part falling within the preset window.

[0083] Specifically, first, the electronic device will use the search window range determined in S501 as the operation template, which clearly defines the start point and end point of data extraction (for example, the Mth sampling point to the Nth sampling point in the time series). Then, the electronic device will traverse each receiving channel marked as synchronization success in S502. For each traversed channel, the electronic device will access the complete cross-correlation result sequence of the channel in the memory. Then, it will use the start and end points of the search window as indexes to perform a slicing operation on the cross-correlation result sequence of the channel, and only copy out the data from the Mth point to the Nth point. This copied out data segment with a length of (N-M+1) is the target cross-correlation result corresponding to the receiving channel in this search window.

[0084] S504: Perform a weighted superposition operation on each target cross-correlation result according to a preset weight coefficient to obtain a total correlation peak value.

[0085] Specifically, first, the electronic device prepares the set of target cross-correlation results (each result is a data sequence of equal length) extracted in S503 for the current search window, and a set of preset weight coefficients corresponding to each of the target cross-correlation results. Then, the electronic device creates an accumulated result sequence of the same length as the target cross-correlation result sequence, with all initial values being zero. Then, for each sample point position in the sequence (for example, from the first point to the last point in the window), the electronic device performs an iteration calculation: it traverses all the receiving channels, takes the cross-correlation value of each channel at the sample point position, and multiplies it by the preset weight coefficient specific to the channel to obtain a weighted value. The electronic device accumulates all the weighted values calculated by the channels to obtain a total correlation peak value.

[0086] S107: Search for the maximum value among all the total correlation peak values, and determine the position corresponding to the maximum value as the final synchronization position.

[0087] Specifically, first, the electronic device takes the total correlation peak value sequence generated in the previous step as the only input data. The sequence can be regarded as a one-dimensional array, where the index of the array represents the time offset, and the value of the array represents the synthesized correlation strength at the time offset. Then, the electronic device performs a maximum value search operation on the array. It starts from the first point of the sequence and traverses the last point one by one, and continuously compares the values of each point in the process. The electronic device maintains a temporary variable to record the maximum value found so far and the position index corresponding to the temporary variable. When a new point is traversed, if the value of the point exceeds the maximum value recorded in the temporary variable, the electronic device updates the temporary variable with the new value and the position index. After completing the traversal of the entire sequence, the position index finally saved in the temporary variable is the position of the maximum value in the entire sequence. The position is then officially designated as the final synchronization position.

[0088] S108: Extract the pilot signals of each receiving antenna according to the final synchronization position, calculate the frequency offset estimation value of each receiving channel according to each pilot signal, and perform a weighted average on the frequency offset estimation values to obtain a final frequency offset estimation value.

[0089] In the embodiments of the present application, the final frequency offset estimation value represents a single, high-precision correction value that is obtained after the optimization and fusion of multiple pieces of information and can represent the comprehensive frequency offset of the entire MIMO system.

[0090] Specifically, first, the electronic device uses the final synchronization position determined in the previous step S107 as the accurate time anchor point. It extracts a corresponding pilot signal from the raw signal data buffered in each receiving antenna (or receiving channel) according to the position of the time anchor point.

[0091] Next, the electronic device independently performs a frequency offset estimation algorithm on each pilot signal segment extracted in the previous step, thereby calculating an initial frequency offset estimation value (for example, foe1, foe2, foe3, etc.) for each receiving channel.

[0092] Then, the electronic device starts the first step of weighted summation. The electronic device acquires the synchronization success flag (Sync_OK, whose value of 1 indicates success and 0 indicates failure) of each receiving channel. It multiplies the frequency offset estimation value (foe_n) of each channel with its corresponding synchronization success flag (Sync_OK(n)), and then adds up the multiplication results of all channels to obtain an accumulated summation result.

[0093] Finally, the electronic device adds up the values of all synchronization success flags (i.e., sum(Sync_OK)), which is actually the total number of successfully synchronized channels. Then, the electronic device divides the accumulated summation result by the total number of channels, and the quotient is the final frequency offset estimation value (foe_A). The formula is expressed as: foe_A = (foe1*Sync_OK(1) + foe2*Sync_OK(2) + foe3*Sync_OK(3) + foe4*Sync_OK(4)) / sum(Sync_OK).

[0094] Based on the above embodiment, as an optional embodiment, S108: calculating the frequency offset estimation value of each receiving channel according to each pilot signal and performing weighted averaging on each frequency offset estimation value to obtain the final frequency offset estimation value, can specifically include the following steps: S601: extracting a corresponding pilot signal from the signal of each receiving channel according to the final synchronization position.

[0095] In the embodiments of the present application, the pilot signal refers to a pre-agreed signal sequence known by the receiving end embedded by the transmitting end at a specific position of the signal frame.

[0096] Specifically, first, the electronic device iterates through each receiving channel and performs the same extraction process for each channel: it takes the final synchronization position as the starting point of reading and continuously reads a signal segment equal to the standard length of the pilot signal. The signal segment read and separated is the pilot signal of the receiving channel at this synchronization position. This process is repeated for all receiving channels to ensure that a set of pilot signals is obtained, each from a different receiving antenna.

[0097] S602: performing frequency offset estimation calculation on each pilot signal segment to obtain a frequency offset estimation value of each receiving channel.

[0098] In the embodiments of the present application, the frequency offset estimation value refers to a value quantifying the deviation between the carrier frequency of the received signal and the frequency of the local oscillator of the receiver.

[0099] Specifically, for a single receiving channel, the calculation process starts with specifying its input data, i.e. the pilot signal segment (a sequence of complex sampling points) extracted for this channel in S601 and the fixed delay D and sampling frequency Fs known by the electronic device. Then, in order to measure the change of phase over time, the electronic device performs an autocorrelation calculation on the pilot signal segment. The core idea of this calculation is to compare the change of the signal before and after the delay: multiply the latter half of the pilot sequence point by point with the conjugate complex of the former half, and then add up all the product results to obtain a complex result R containing key phase information. Then, the electronic device extracts the phase angle ΔΦ from this complex R, and this angle value accurately represents the total phase rotation amount accumulated due to the frequency deviation within the time corresponding to the delay D. Finally, based on the physical principle that frequency is the rate of change of phase, the electronic device divides this total phase rotation amount ΔΦ by the time it takes to generate (i.e. D / Fs), and the final value obtained is the frequency offset estimation value of this receiving channel.

[0100] S603: obtaining the synchronization flag bit of each receiving channel, multiplying the frequency offset estimation value of each receiving channel by the corresponding synchronization flag bit, and then performing accumulation summation to obtain an accumulation summation result.

[0101] In the embodiments of the present application, the synchronization flag bit represents a binary status bit used to identify whether the corresponding receiving channel has successfully established a reliable synchronization connection with the signal of the transmitting end.

[0102] Specifically, two data sets are obtained: one is a set of frequency offset estimation values (such as foe1, foe2, foe3...) calculated for all receiving channels in S602, and the other is the synchronization flag bit (such as flag1, flag2, flag3...) corresponding to each channel generated by the electronic device synchronization module. Then, the electronic device performs a weighted calculation for each channel, that is, the frequency offset estimation value of the channel is multiplied by the synchronization flag bit corresponding thereto. This multiplication operation realizes the core filtering logic: if the synchronization flag bit of a channel is a synchronization success flag bit, which is "1", the frequency offset estimation value will be kept intact (foe*1=foe); and if the synchronization flag bit is not a synchronization success flag bit, which is "0", the frequency offset estimation value will be directly cleared (foe*0=0), and thus effectively excluded from subsequent calculations. After completing this filtering step for all channels, the electronic device will accumulate and sum all the values obtained by the multiplication operation to obtain an accumulated sum result, which only contains the sum of the frequency offset information of the channels authenticated as reliable by the synchronization success flag bit, and lays a foundation for obtaining a more accurate final frequency offset compensation value.

[0103] S604: Divide the accumulated sum result by the sum of all synchronization success flag bits to obtain the final frequency offset estimation value.

[0104] Specifically, the electronic device takes the accumulated sum result output by the previous step S603 as the dividend (numerator), which collects the frequency offset estimation value information of all reliable channels. At the same time, the electronic device adds the synchronization flag bits (a series of "1" and "0") of all receiving channels to obtain the total number of synchronized channels, and takes this as the divisor (denominator). Then, a division operation is performed, that is, the accumulated frequency offset sum is divided by the number of successful channels. The core purpose of this averaging process is to smooth and suppress the random noise or small measurement errors that may exist in a single channel by integrating the data of multiple reliable sources, so as to obtain a more stable and accurate frequency offset than any single channel estimation. The final quotient of the division operation is a value optimized by multi-source information fusion, that is, the final frequency offset estimation value.

[0105] Figure 3 is an exemplary MIMO synchronization process flow chart of a dual-antenna provided by an embodiment of the present application; The flow chart details a synchronization and frequency offset estimation algorithm for a dual-antenna system. The entire process begins with two independent signal sources: receive antenna ra=1 and receive antenna ra=2. Take the processing path of receive antenna ra=1 as an example. The received signal is sent into four independent synchronization search engines, namely SEQ1, SEQ2, SEQ3 and SEQ4, in parallel. Each search engine works independently and produces its own frequency offset estimation value and success flag: SEQ1 produces foe1 and flag1; SEQ2 produces foe2 and flag2; SEQ3 produces foe3 and flag3; and SEQ4 produces foe4 and flag4. At the same time, the signal from receive antenna ra=2 also goes through a similar parallel processing structure, and the multiple sets of results produced will enter the subsequent fusion stage together with the results of receive antenna ra=1. In the first step of data fusion, i.e. S603: accumulation and summation stage, the system will collect all the frequency offset estimation values output by the search engines (such as foe1, foe2, foe3, foe4, etc.) and their respective flags (such as flag1, flag2, flag3, flag4, etc.), and obtain a weighted sum by multiplying each frequency offset estimation value with its flag and then adding them all together. Then, the result of the accumulation and summation is sent to S604: average value stage, in which the result is divided by the total sum of all successful flags (i.e. the number of flags with a value of 1). Through this average value operation, the system finally calculates a single and accurate final frequency offset estimation value.

[0106] An exemplary multi-antenna MIMO architecture synchronization device provided by the embodiment of the present application is introduced below. Figure 4 FIG. 1 is an exemplary hardware structure schematic diagram of a multi-antenna MIMO architecture synchronization device provided by the embodiment of the present application.

[0107] In some embodiments, the multi-antenna MIMO architecture synchronization device is a computer device or includes a computer device in the multi-antenna MIMO architecture synchronization device. The computer device includes a processor, a memory, and a network interface connected through a system bus. The processor of the computer device is configured to provide computing and control capabilities. The memory of the computer device includes a non-volatile storage medium and an internal memory. The non-volatile storage medium stores an operating system, a computer program, and a database. The internal memory provides an environment for running the operating system and the computer program in the non-volatile storage medium. The database of the computer device is configured to store data. The network interface of the computer device is configured to communicate with other terminals or servers outside through a network connection. In some embodiments, the network interface can be a wired network interface, and in some embodiments, the network interface can also be a wireless network interface. The computer program is executed by the processor to implement the method in the embodiment of the present application.

[0108] Those skilled in the art can understand that Figure 4 The structure shown in the figure is only a block diagram of part of the structure related to the scheme of the present application, and does not constitute a limitation on the computer device to which the scheme of the present application is applied. A specific computer device can include more or fewer components than those shown in the figure, or combine certain components, or have a different arrangement of components.

[0109] The above-described embodiments are only used to illustrate the technical scheme of the present application, but not limit it; although the technical scheme recorded in the foregoing embodiments has been described in detail, those skilled in the art should understand that it can still be modified or equivalent replaced for part of the technical features; and these modifications or replacements do not make the essence of the corresponding technical scheme deviate from the scope of the technical scheme of the embodiments of the present application.

[0110] In the above embodiments, according to the context, the term "when" can be interpreted as meaning "if" or "after" or "in response to determining" or "in response to detecting". Similarly, according to the context, the phrase "on determining" or "if detecting (the stated condition or event)" can be interpreted as meaning "if determining" or "in response to determining" or "on detecting (the stated condition or event)" or "in response to detecting (the stated condition or event)".

[0111] In the above embodiments, all or part of the technical scheme can be implemented by software, hardware, firmware or any combination thereof. When implemented by software, all or part of the technical scheme can be implemented in the form of a computer program product. The computer program product includes one or more computer instructions. When the computer program instructions are loaded and executed on a computer, all or part of the processes or functions described in the embodiments of the present application are generated. The computer can be a general-purpose computer, a special-purpose computer, a computer network, or other programmable devices. The computer instructions can be stored in a computer readable storage medium or transmitted from one computer readable storage medium to another computer readable storage medium, for example, the computer instructions can be transmitted from one website, computer, server or data center to another website, computer, server or data center through wired (such as coaxial cable, optical fiber, digital subscriber line) or wireless (such as infrared, wireless, microwave, etc.) mode. The computer readable storage medium can be any available medium that can be accessed by a computer or a data storage device such as a server, data center, etc. integrated with one or more available media. The available media can be magnetic media (for example, floppy disk, hard disk, magnetic tape), optical media (for example, DVD), or semiconductor media (for example, solid state disk) and the like.

[0112] Those skilled in the art can understand that all or part of the processes in the above-mentioned method embodiments can be implemented by a computer program instructing relevant hardware to complete, the program can be stored in a computer readable storage medium, and the program can include the processes of the above-mentioned method embodiments when executed. The aforementioned storage medium includes ROM or random storage memory RAM, magnetic disc or optical disc and various storage code medium.

Claims

1. A synchronization method for a multi-antenna MIMO architecture, characterized in that, The method includes: The sampling signal is received through multiple receiving channels, the number of which is the product of the number of transmitting antennas and the number of receiving antennas; The sampled signals are downsampled to obtain downsampled signals; Multiple buffers are designated to store each of the downsampled signals, and the number of buffers is equal to the number of receiving channels; When the downsampled signal exists in all buffers, the downsampled signal is cross-correlated with the local synchronization time domain signal to obtain the cross-correlation result on each receiving channel; When any of the receiving channels detects a valid peak value, the position of the valid peak value is determined as the preliminary synchronization position. The valid peak value refers to the peak value that meets the preset conditions in each of the cross-correlation results. Based on the initial synchronization positions, the corresponding search window range is determined. The target cross-correlation results of each receiving channel marked as successfully synchronized are weighted and superimposed within the search window range to obtain the overall correlation peak value corresponding to each search window range. Search for the maximum value among all overall correlation peaks, and determine the position corresponding to the maximum value as the final synchronization position; The pilot signals of each receiving channel are extracted based on the final synchronization position. The frequency offset estimate of each receiving channel is calculated based on the pilot signals, and the frequency offset estimate is weighted and averaged to obtain the final frequency offset estimate.

2. The synchronization method for a multi-antenna MIMO architecture according to claim 1, characterized in that, The step of performing cross-correlation calculations between each of the downsampled signals and the local synchronization time-domain signal to obtain the cross-correlation results on each of the receiving antennas includes: According to the first formula, cross-correlation calculation is performed on each of the downsampled signals and the local synchronization time domain signal to obtain the cross-correlation results on each of the receiving antennas; The first formula is: Wherein, SEQ(n) p This refers to the cross-correlation result of the p-th receiving channel at sampling time n, where n is the sampling time, p is the index of the receiving channel, M is the length of the local synchronization sequence, m is the position index in the local synchronization sequence, and S... Q (Qm+n) represents the downsampled signal of the p-th receiving channel at time Qm+n, where Q is the sampling interval parameter, and h is the sampling interval parameter. * (m) represents the conjugate of the local synchronization time-domain signal, N is the search range, and M... ant This represents the total number of receiving channels.

3. The synchronization method for a multi-antenna MIMO architecture according to claim 1, characterized in that, The effective peak value refers to the peak value that meets the preset conditions among the cross-correlation results, including: Determine the peak detection parameters, which include an absolute threshold and a relative threshold; The maximum value of each cross-correlation result is searched within a preset time range to obtain the candidate peak value and the position of the candidate peak value; When the candidate peak value is greater than the absolute threshold, and the ratio of the candidate peak value to the average value of all candidate peak values ​​is greater than the relative threshold, the candidate peak value is determined to be a valid peak value.

4. The synchronization method for a multi-antenna MIMO architecture according to claim 3, characterized in that, After determining the candidate peak value as a valid peak value, the method further includes: Calculate the offset between the position of the effective peak and the final synchronization position obtained from the previous wireless frame time; When the offset is less than the preset offset threshold, the position of the effective peak is confirmed to be valid, and the position of the effective peak within the preset time range is recorded.

5. The synchronization method for a multi-antenna MIMO architecture according to claim 1, characterized in that, The step of determining the search window range based on the preliminary synchronization position, and then weighting and summing the target cross-correlation results of each of the receiving channels marked as successfully synchronized within the search window range to obtain the overall correlation peak value includes: A search window of a preset length is set with the initial synchronization position as the center; The receiving channel that detected the effective peak value is marked as successfully synchronized; Extract the target cross-correlation results corresponding to each of the receiving channels marked as successfully synchronized within the search window; The cross-correlation results of each target are weighted and superimposed according to a preset weighting coefficient to obtain the overall correlation peak value.

6. The synchronization method for a multi-antenna MIMO architecture according to claim 1, characterized in that, The step of extracting the pilot signals of each receiving channel based on the final synchronization position, calculating the frequency offset estimate of each channel, and performing a weighted average to obtain the final frequency offset estimate includes: Based on the final synchronization position, extract the corresponding pilot signal from the signals of each of the receiving channels; Frequency offset estimation is performed on each of the pilot signal segments to obtain the frequency offset estimate value of each receiving channel; Obtain the synchronization flag bit of each of the receiving channels, multiply the frequency offset estimate of each of the receiving channels by the corresponding synchronization flag bit, and then sum them up to obtain the summation result; Divide the summation result by the sum of all synchronization success flags to obtain the final frequency offset estimate.

7. The synchronization method for a multi-antenna MIMO architecture according to claim 1, characterized in that, The step of downsampling each of the sampled signals to obtain a downsampled signal includes: Each of the sampled signals is subjected to low-pass filtering to filter out signals outside the local synchronization signal frequency band. The cutoff frequency of the low-pass filter is set to the bandwidth of the local synchronization signal. Set the downsampling factor, and perform downsampling processing on the low-pass filtered signal according to the downsampling factor, so that the rate of the downsampled signal is a preset multiple of the sampling factor of the local synchronous time domain signal, and obtain the downsampled signal.

8. A synchronization device with a multi-antenna MIMO architecture, characterized in that, The multi-antenna MIMO architecture synchronization device includes: one or more processors and a memory; the memory is coupled to the one or more processors, the memory is used to store computer program code, the computer program code including computer instructions, and the one or more processors call the computer instructions to cause the multi-antenna MIMO architecture synchronization device to perform the method as described in any one of claims 1-7.

9. A computer program product containing instructions, characterized in that, When the computer program product is run on a multi-antenna MIMO architecture synchronization device, the multi-antenna MIMO architecture synchronization device performs the method as described in any one of claims 1-7.

10. A computer-readable storage medium comprising instructions, characterized in that, When the instruction is executed on a multi-antenna MIMO architecture synchronization device, the multi-antenna MIMO architecture synchronization device performs the method as described in any one of claims 1-7.

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