High-efficiency wide-load constant-voltage multi-voltage output MCR-WPT system and control method thereof

Abstract

The invention relates to a high-efficiency wide-load constant-voltage multi-voltage output MCR-WPT system and a control method thereof, and the system comprises an H-bridge high-frequency inversion module which is used for outputting a high-frequency alternating current to an MCR-WPT module under the driving of a primary side closed-loop control module; the MCR-WPT module is used for regulating the voltage of the high-frequency alternating current and then transmitting the high-frequency alternating current to the full-bridge synchronous rectification module; the full-bridge synchronous rectification module is used for rectifying the high-frequency alternating current and then inputting the rectified high-frequency alternating current to the Boost converter module; the secondary side closed-loop control module is used for outputting a control signal according to the load output information; the Boost converter module is used for realizing voltage stabilization under the action of a control signal of the secondary side closed-loop control module and transmitting the voltage to a load; and the primary side closed-loop control module is used for realizing high-efficiency wide-load constant-voltage multi-voltage output of the system according to the load output information. According to the invention, the problem that the MCR-WPT system is difficult to realize multi-voltage high-efficiency constant-voltage output at the same time when the input voltage or the load fluctuates is effectively solved.

Description

Technical Field

[0001] This invention relates to the field of wireless power transmission technology, and in particular to a high-efficiency, wide-load constant-voltage multi-voltage output MCR-WPT system and its control method. Background Technology

[0002] Magnetic Coupling Resonant Wireless Power Transfer (MCR-WPT) technology enables contactless power transfer based on near-field electromagnetic coupling. Due to its advantages such as long transmission range, excellent transmission efficiency, and high security, it holds a key position in the field of power transfer and is widely used in various scenarios.

[0003] In practical applications, most electrical devices require power supplies with efficient constant voltage output characteristics, meaning the output voltage is unaffected by changes in load and other parameters, and the transmission efficiency remains high. Furthermore, it needs to adapt to multiple voltage levels such as 6V, 12V, and 24V. Wireless power transfer technology, through compensation network design and voltage regulation circuit control, can adjust the output voltage according to the charging requirements of different devices, thus meeting their charging needs.

[0004] Currently, the main methods for achieving efficient constant voltage output of a system using wireless power transfer technology are: 1. Achieving constant voltage output under fixed gain through fixed parameter optimization, but this method suffers from large output power fluctuations; 2. Aiming at maximum efficiency tracking, using real-time adjustment strategies to compensate for output fluctuations, but the above control strategies often require dual DC-DC converters. Simple control can easily lead to insufficient output voltage stability, while complex control can increase system costs and introduce additional power losses; 3. Aiming at both efficiency and voltage control, combining system structure and control strategies to achieve constant voltage output and efficiency optimization, but this method is mostly based on ideal operating condition modeling, lacks universality, and complex control logic can easily lead to large overshoot and long settling time. At the same time, complex circuit structures increase hardware costs.

[0005] In summary, while numerous studies by domestic and international scholars have addressed the high efficiency and constant voltage output of traditional MCR-WPT systems, existing technologies still suffer from problems such as large power fluctuations, insufficient stability, high cost, and weak versatility, making it difficult to meet the practical application requirements for efficient and constant voltage output across a wide load range. To overcome these shortcomings, this invention, based on MCR-WPT technology and combined with control technology, proposes a high-efficiency, wide-load constant voltage multi-voltage output MCR-WPT system and its control method. This effectively solves the problem that MCR-WPT systems struggle to simultaneously achieve efficient and constant voltage output across multiple voltages when the input voltage or load fluctuates. Summary of the Invention

[0006] The purpose of this invention is to provide a high-efficiency, wide-load constant-voltage multi-voltage output MCR-WPT system and its control method. Addressing the problems of system output fluctuation and efficiency degradation caused by input fluctuations or load changes, this invention utilizes a single-transmitter, dual-parallel pickup MCR-WPT system circuit model and introduces a transformer T-equivalent network model to achieve multi-voltage constant-voltage output. Primary and secondary side dual closed-loop control is employed to solve the voltage fluctuation problem of the T-type equivalent network, shortening the adjustment time to reduce transition losses. These three elements work together to achieve stable multi-voltage output and improve system efficiency. The system possesses the characteristics of high-efficiency, wide-load constant-voltage output, variable-gain multi-voltage output, simplified circuit structure, and low cost, thus overcoming the shortcomings of existing technologies.

[0007] To achieve the above objectives, the present invention provides the following solution:

[0008] A high-efficiency, wide-load constant-voltage multi-voltage output MCR-WPT system includes: an H-bridge high-frequency inverter module, an MCR-WPT module, a full-bridge synchronous rectifier module, a Boost converter module, a primary-side closed-loop control module, and a secondary-side closed-loop control module.

[0009] The H-bridge high-frequency inverter module is used to output high-frequency AC power to the MCR-WPT module under the drive of the primary-side closed-loop control module.

[0010] The MCR-WPT module is used to transmit the regulated high-frequency AC power to the full-bridge synchronous rectification module;

[0011] The full-bridge synchronous rectification module is used to rectify the high-frequency AC power and input it to the Boost converter module;

[0012] The secondary closed-loop control module is used to output control signals based on load output information;

[0013] The Boost converter module is used to achieve voltage regulation and transmit it to the load under the control signal of the secondary closed-loop control module.

[0014] The primary-side closed-loop control module is used to achieve efficient, wide-load constant voltage multi-voltage output of the system based on the load output information.

[0015] Optionally, the H-bridge high-frequency inverter module includes: a first switching transistor S1, a second switching transistor S2, a third switching transistor S3, and a fourth switching transistor S4; the first switching transistor S1 and the third switching transistor S3 are connected in series, the second switching transistor S2 and the fourth switching transistor S4 are connected in series, and the series branch of the first switching transistor S1 and the third switching transistor S3 is connected in parallel with the series branch of the second switching transistor S2 and the fourth switching transistor S4.

[0016] Optionally, the MCR-WPT module includes: a transmitting coil L1, a first capacitor C1, a transmitting coil internal resistance R1, a first pickup coil L2, a first pickup coil internal resistance R2, a second capacitor C2, a second pickup coil L3, a second pickup coil internal resistance R3, and a third capacitor C3.

[0017] Among them, the mutual inductance M between the transmitting coil L1 and the first picking coil L2 is... 12 The mutual inductance M between the first pickup coil L2 and the second pickup coil L3 23 The mutual inductance M between the transmitting coil L1 and the second picking coil L3 13 The transmitting coil L1 is connected in series with the first capacitor C1 and the internal resistance R1 of the transmitting coil; the first pickup coil L2 is connected in series with the internal resistance R2 of the first pickup coil and the second capacitor C2; the second pickup coil L3 is connected in series with the internal resistance R3 of the second pickup coil and the third capacitor C3; and the second capacitor C2 is connected in series with the third capacitor C3.

[0018] Optionally, the full-bridge synchronous rectification module includes: a fifth switching transistor Q1, a sixth switching transistor Q2, a seventh switching transistor Q3, an eighth switching transistor Q4, and a fourth capacitor C4; the fifth switching transistor Q1 and the seventh switching transistor Q3 are connected in series, the sixth switching transistor Q2 and the eighth switching transistor Q4 are connected in series, the series branch of the fifth switching transistor Q1-the seventh switching transistor Q3 and the series branch of the sixth switching transistor Q2-the eighth switching transistor Q4 are connected in parallel, and then connected in parallel with the fourth capacitor C4.

[0019] Optionally, the Boost converter module includes: inductor L4, ninth switching transistor T1, diode D5, fifth capacitor C5, and load resistor R. L The fifth capacitor C5 and the load resistor R L Parallel connection, parallel branch C5-R L The ninth switching transistor T1 is connected in parallel with diode D5, and the parallel branch D5-T1 is connected in series with inductor L4.

[0020] Optionally, the primary-side closed-loop control module includes: a primary-side ADS1115 chip, a data comparator, an STM32 microprocessor, and an IR2110 chip connected in sequence to form a primary-side closed-loop control path.

[0021] The secondary-side closed-loop control module includes a secondary-side ADS1115 chip and a PWM controller; the ADS1115 chip and the PWM controller are connected in sequence to form a secondary-side closed-loop control path.

[0022] This invention also provides a control method for a high-efficiency, wide-load constant-voltage multi-voltage output MCR-WPT system, comprising:

[0023] The H-bridge high-frequency inverter module, driven by the primary-side closed-loop control module, inverts DC power into high-frequency AC power for the MCR-WPT module. The MCR-WPT module then regulates the voltage of the high-frequency AC power and transmits it to the full-bridge synchronous rectifier module. The full-bridge synchronous rectifier module rectifies the AC power and transmits it to the Boost converter module. Under the control signal of the secondary-side closed-loop control module, the Boost converter module stabilizes the voltage and transmits it to the load. It then transmits the load output information collected by the secondary-side closed-loop control module to the primary-side closed-loop control module, ultimately achieving efficient, wide-load, constant-voltage multi-voltage output.

[0024] Optionally, the MCR-WPT module includes the following high-frequency AC voltage regulation:

[0025] The equivalent impedance matrix equation is established based on the equivalent model of the transformer T network, and the parameters of the resonant capacitor with constant voltage characteristics are obtained.

[0026] The high-frequency AC voltage is adjusted according to the parameters of the resonant capacitor with constant voltage characteristics.

[0027] The parameters of the resonant capacitor with constant voltage characteristics are as follows:

[0028]

[0029] In the formula, C 41 Here, ω is the compensation capacitor value of the transmitter circuit, ω is the system operating frequency, n is the variable gain coefficient, L1 is the transmitting coil, and M is the value of the transmitter circuit compensation capacitor. 12 For the mutual inductance between the transmitting coil L1 and the first picking coil L2, M 13 For the mutual inductance between the transmitting coil L1 and the second picking coil L3, C 42 The receiving end circuit compensation capacitor value is L2, the first pickup coil is L3, the second pickup coil is M. 23 The first pickup coil L2 and the second pickup coil L3 are mutually inducted.

[0030] Optionally, the Boost converter module, under the control signal of the secondary-side closed-loop control module, achieves voltage regulation and transmits the voltage to the load, including:

[0031] The secondary-side closed-loop control module samples the voltage / current information output by the load through the secondary-side ADC1115 chip and transmits it to the PWM controller. The PWM controller outputs a control signal to drive the switching of the ninth switching transistor T1 in the Boost converter module.

[0032] When the ninth switching transistor T1 is turned on, the inductor L4 stores energy, and the diode D5 is turned off to prevent the energy from flowing back into the fifth capacitor C5;

[0033] When the ninth switching transistor T1 is turned off, the inductor L4 releases energy, the diode D5 turns on and guides the inductor energy into the fifth capacitor C5. At the same time, the fifth capacitor C5 smooths the output voltage ripple and finally transmits the regulated electrical energy to the load.

[0034] Optionally, the PWM controller includes: an inner current loop control unit, an outer voltage loop control unit, and a feedforward compensation unit;

[0035] The inner loop control unit adjusts the current loop proportional coefficient K. p,i Integral coefficient K of the current loop i,i To handle current deviations;

[0036] The voltage outer loop control unit uses the voltage loop integral coefficient K. i Eliminate steady-state error of output voltage;

[0037] The feedforward compensation unit uses the feedforward compensation amount d ff To counteract disturbances;

[0038] Wherein, the current loop proportionality coefficient K p,i Integral coefficient K of the current loop i,i for:

[0039]

[0040] The voltage loop integral coefficient K i for:

[0041]

[0042] The feedforward compensation amount d ff for:

[0043]

[0044] Among them, L eq The equivalent leakage inductance L4 is the voltage induced by the leakage flux on the secondary side. sk The equivalent inductance formed by the combination, U tri ω is the carrier amplitude. ci U is the bandwidth of the current loop. L R is the output voltage of the Boost converter module, D is the duty cycle of the PWM controller output, and R is the output voltage of the Boost converter module. L For system load, ω cv K represents the voltage loop bandwidth, ΔU3 is the deviation between the actual value of the input voltage U3 and the set stable reference value of U3, and K is the voltage loop bandwidth. p This is the voltage loop proportionality coefficient.

[0045] The beneficial effects of this invention are as follows: Addressing the voltage regulation requirements of wireless power transmission systems under input or load fluctuations, this invention is based on a single-transmitter secondary-side dual-parallel pickup MCR-WPT circuit model design, requiring only a single voltage regulator circuit to meet multiple voltage output needs. Simultaneously, combined with the dual-closed-loop collaborative control of the primary and secondary-side control modules, the system achieves efficient constant voltage output while simultaneously realizing multiple voltage outputs. Furthermore, the overall circuit structure is simplified, hardware costs are low, and it possesses adaptive adjustment capabilities, effectively solving the problems of complex structure and high cost caused by the need for multiple voltage regulator circuits in existing systems.

[0046] This invention, through the rational design of the resonant parameters of the MCR-WPT module, the component parameters of the Boost converter, and the PI parameters of the PWM controller, achieves zero-voltage turn-on of the switching transistors in the H-bridge high-frequency inverter module, significantly reducing switching losses. Furthermore, under dynamic operating conditions, it ensures efficient constant voltage output and soft-switching characteristics, further widening the voltage output range, reducing the number of dynamic tuning cycles, lowering transition losses, and ultimately improving the overall transmission efficiency of the system. This overcomes the shortcomings of existing technologies, such as low efficiency and narrow voltage output range under dynamic conditions. Attached Figure Description

[0047] To more clearly illustrate the technical solutions in the embodiments of the present invention or the prior art, the drawings used in the embodiments will be briefly introduced below. Obviously, the drawings described below are only some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0048] Figure 1 This is a schematic diagram of a high-efficiency, wide-load constant voltage, multi-voltage output MCR-WPT system framework according to an embodiment of the present invention;

[0049] Figure 2 This is a circuit diagram of a high-efficiency, wide-load constant voltage, multi-voltage output MCR-WPT system according to an embodiment of the present invention;

[0050] Figure 3 The diagram shows the equivalent circuit and transformer T-network model of the single-transmitter dual-parallel pickup MCR-WPT system according to an embodiment of the present invention. (a) is the equivalent circuit diagram of the single-transmitter dual-parallel pickup MCR-WPT system, (b) is the simplified circuit diagram of the single-transmitter dual-parallel pickup MCR-WPT system, and (c) is the circuit diagram of the single-transmitter dual-parallel pickup MCR-WPT system based on the transformer T-network model.

[0051] Figure 4 This is a schematic diagram of a high-efficiency, wide-load constant voltage, multi-voltage output MCR-WPT system PWM controller according to an embodiment of the present invention;

[0052] Figure 5 The following are experimental waveform diagrams of an efficient wide-load constant voltage multi-voltage output MCR-WPT system and its control method according to an embodiment of the present invention: (a) is the equivalent circuit diagram of the single-transmitter dual-parallel pickup MCR-WPT system; (b) is the simplified circuit diagram of the single-transmitter dual-parallel pickup MCR-WPT system; and (c) is the circuit diagram of the single-transmitter dual-parallel pickup MCR-WPT system based on the transformer T-network model. Detailed Implementation

[0053] The technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some embodiments of the present invention, and not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of the present invention.

[0054] To make the above-mentioned objects, features and advantages of the present invention more apparent and understandable, the present invention will be further described in detail below with reference to the accompanying drawings and specific embodiments.

[0055] This embodiment provides a high-efficiency, wide-load constant voltage multi-voltage output MCR-WPT system, including: an H-bridge high-frequency inverter module, an MCR-WPT module, a full-bridge synchronous rectification module, a Boost converter module, a primary-side closed-loop control module, and a secondary-side closed-loop control module;

[0056] The H-bridge high-frequency inverter module is used to output high-frequency AC power to the MCR-WPT module under the drive of the primary-side closed-loop control module.

[0057] The MCR-WPT module is used to transmit high-frequency AC voltage after voltage regulation to the full-bridge synchronous rectifier module;

[0058] The full-bridge synchronous rectifier module is used to rectify high-frequency AC power and input it to the Boost converter module;

[0059] The secondary closed-loop control module is used to output control signals based on load output information;

[0060] The Boost converter module is used to achieve voltage regulation and transmit the voltage to the load under the control signal of the secondary closed-loop control module;

[0061] The primary-side closed-loop control module is used to achieve efficient, wide-load constant voltage multi-voltage output of the system based on load output information.

[0062] Furthermore, the system in this embodiment also includes an input module that provides input voltage to the H-bridge high-frequency inverter module. The input module includes a 12V DC source U. s and DC source internal resistance R s The DC source Us and DC source internal resistance R s Series connection.

[0063] The load module includes a load resistor R L .

[0064] The wireless transmission module transmits the load output information to the primary-side closed-loop control module. The wireless transmission module includes a secondary-side ESP8266 chip and a primary-side ESP8266 chip. The secondary-side ESP8266 chip and the primary-side ESP8266 chip transmit data via WIFI.

[0065] Furthermore, the H-bridge high-frequency inverter module includes: a first switching transistor S1, a second switching transistor S2, a third switching transistor S3, and a fourth switching transistor S4; the first switching transistor S1 and the third switching transistor S3 are connected in series, the second switching transistor S2 and the fourth switching transistor S4 are connected in series, and the series branch of the first switching transistor S1 and the third switching transistor S3 is connected in parallel with the series branch of the second switching transistor S2 and the fourth switching transistor S4.

[0066] Furthermore, the MCR-WPT module includes: a transmitting coil L1, a first capacitor C1, a transmitting coil internal resistance R1, a first pickup coil L2, a first pickup coil internal resistance R2, a second capacitor C2, a second pickup coil L3, a second pickup coil internal resistance R3, and a third capacitor C3.

[0067] Among them, the mutual inductance M between the transmitting coil L1 and the first picking coil L2 is... 12 The mutual inductance M between the first pickup coil L2 and the second pickup coil L3 23 The mutual inductance M between the transmitting coil L1 and the second picking coil L3 13 The transmitting coil L1 is connected in series with the first capacitor C1 and the internal resistance R1 of the transmitting coil; the first pickup coil L2 is connected in series with the internal resistance R2 of the first pickup coil and the second capacitor C2; the second pickup coil L3 is connected in series with the internal resistance R3 of the second pickup coil and the third capacitor C3; the second capacitor C2 is connected in series with the third capacitor C3; the L2-R2-C2 series branch is connected in parallel with the L3-R3-C3 series branch.

[0068] Furthermore, the full-bridge synchronous rectification module includes: a fifth switching transistor Q1, a sixth switching transistor Q2, a seventh switching transistor Q3, an eighth switching transistor Q4, and a fourth capacitor C4; the fifth switching transistor Q1 and the seventh switching transistor Q3 are connected in series, the sixth switching transistor Q2 and the eighth switching transistor Q4 are connected in series, the series branch of the fifth switching transistor Q1-the seventh switching transistor Q3 and the series branch of the sixth switching transistor Q2-the eighth switching transistor Q4 are connected in parallel, and then connected in parallel with the fourth capacitor C4.

[0069] Furthermore, the Boost converter module includes: inductor L4, ninth switching transistor T1, diode D5, fifth capacitor C5, and load resistor R. L The fifth capacitor C5 and the load resistor R L Parallel connection, parallel branch C5-R L The diode D5 is connected in series, the ninth switching transistor T1 is connected in parallel with the diode D5, and the parallel branch D5-T1 is connected in series with the inductor L4.

[0070] Furthermore, the primary-side closed-loop control module includes: a primary-side ADS1115 chip connected in sequence for acquiring the output voltage U1 of the H-bridge inverter module; and a data comparator for receiving the output voltage U1 of the primary-side ADS1115 chip and comparing U1 with U... L The STM32 microprocessor receives the comparison result from the primary-side ADS1115 chip and sends a PWM signal based on the comparison result; the IR2110 chip amplifies the PWM signal sent by the STM32 microprocessor to drive Q1 to Q4, forming a primary-side closed-loop control path.

[0071] The secondary closed-loop control module includes: a secondary ADS1115 chip and a PWM controller; the ADS1115 chip and the PWM controller are connected in sequence to form a secondary closed-loop control path.

[0072] The following description, in conjunction with the accompanying drawings, further illustrates this embodiment:

[0073] A high-efficiency, wide-load constant-voltage, multi-voltage output MCR-WPT system, such as Figure 1-3 As shown, it includes: an input module, an H-bridge high-frequency inverter module, an MCR-WPT module, a full-bridge synchronous rectification module, a Boost converter module, a load module, a secondary-side closed-loop control module, a wireless transmission module, and a primary-side closed-loop control module.

[0074] The input module includes a 12V DC power supply U s and DC source internal resistance R s ;

[0075] DC source U s and DC source internal resistance R s Series;

[0076] The input module transmits 12V DC power to the H-bridge high-frequency inverter module;

[0077] The primary-side closed-loop control module consists of a primary-side ADS1115 chip, an STM32 microprocessor, and an IR2110 chip.

[0078] The primary-side ADS1115 chip, STM32 microprocessor and IR2110 chip are connected in sequence to form a primary-side closed-loop control path;

[0079] The primary-side closed-loop control module acquires the output voltage of the H-bridge high-frequency inverter module through the ADS1115 chip, compares it with the secondary-side output voltage transmitted by the wireless transmission module, and transmits the comparison information to the STM32 microprocessor. The STM32 microprocessor generates a PWM signal and transmits it to the drive circuit composed of the IR2110 chip. The drive circuit outputs a drive signal to the H-bridge high-frequency inverter module.

[0080] The H-bridge high-frequency inverter module includes a first switching transistor S1, a second switching transistor S2, a third switching transistor S3, and a fourth switching transistor S4.

[0081] The first switching transistor S1 is connected in series with the third switching transistor S3, the second switching transistor S2 is connected in series with the fourth switching transistor S4, and the S1-S3 series branch and the S2-S4 series branch are connected in parallel.

[0082] The H-bridge high-frequency inverter module receives the drive signal from the primary-side control module and drives S1 and S3, S2 and S4 to conduct alternately, inverting the 12V DC power input from input module 1 into high-frequency AC power with a frequency of 100kHz and a peak-to-peak value of 24V, and transmitting it to the MCR-WPT module.

[0083] The MCR-WPT module 3 includes a transmitting coil L1, a first capacitor C1, a transmitting coil internal resistance R1, a first pickup coil L2, a first pickup coil internal resistance R2, a second capacitor C2, a second pickup coil L3, a second pickup coil internal resistance R3, a third capacitor C3, and a mutual inductance M between the transmitting coil and the first pickup coil. 12 The mutual inductance M between the first pickup coil and the second pickup coil 23 The mutual inductance M between the transmitting coil and the second pickup coil 13 ;

[0084] The transmitting coil L1, the first capacitor C1, and the internal resistance R1 of the transmitting coil are connected in series. The first pickup coil L2, the internal resistance R2 of the first pickup coil, and the second capacitor C1 are connected in series. The second pickup coil L3, the internal resistance R3 of the second pickup coil, and the third capacitor C3 are connected in series. The L2-R2-C2 series branch and the L3-R3-C3 series branch are connected in parallel.

[0085] The MCR-WPT module receives high-frequency AC power of 100kHz and 24V peak-to-peak from the H-bridge high-frequency inverter module. It first passes through C1 for filtering, and then transmits the AC power to L2 and L3 through electromagnetic coupling. Finally, the high-frequency AC power is transmitted to the full-bridge synchronous rectifier module.

[0086] For the single-transmit dual-parallel pickup MCR-WPT system, according to Figure 3 (a) Equivalent circuit diagram of a single-emitter dual-parallel pickup MCR-WPT system and Figure 3(b) Simplified circuit diagram of single-emitter dual-parallel pickup MCR-WPT system, the matrix equations are established as follows:

[0087]

[0088] Z eq1 C is the equivalent impedance value after the two receiving coils are connected in parallel. 24 If the receiving end loop is a compensation capacitor, then the system loop current is:

[0089]

[0090] This leads to the derivation of the system transmission efficiency:

[0091]

[0092] The optimal equivalent load resistance value is:

[0093]

[0094] Although the traditional three-coil mutual inductance model can characterize the coupling relationship between coils, the cross-coupling effect is significant and it is difficult to meet the design requirements of multiple voltage outputs. Therefore, a transformer T-type equivalent network model is further introduced. By co-optimizing the compensation capacitor parameters and the equivalent turns ratio, the calculation formula of the system compensation parameters is derived, providing theoretical support for wide-range voltage regulation.

[0095] In the design of constant voltage characteristics of the MCR-WPT system, the parameters of the resonant capacitor must first meet the resonance requirements of the circuit at the operating frequency. This is the basis for achieving constant voltage characteristics. Its value needs to be determined in combination with the self-inductance of the transmitting and receiving coils.

[0096] n is related to the mutual inductance between the coils, and the mutual inductance is related to the self-inductance of the transmitting and receiving coils. Therefore, n will indirectly be related to the self-inductance of the coil that determines the resonant capacitance. Thus, by deriving the expression for the compensation capacitor parameter containing n, the compensation capacitor value corresponding to the variable gain coefficient can be calculated. Then, by changing the resonant capacitor value, constant voltage output with different equivalent turns ratios can be achieved.

[0097] Neglecting the parasitic resistance of each coil, according to Figure 3 (c) shows the circuit diagram of the single-emitter dual-parallel pickup MCR-WPT system based on the transformer T-network model. The equivalent impedance matrix equation is established as follows:

[0098]

[0099] Through equivalent transformation of circuit parameters, we can obtain:

[0100]

[0101] Because of ωC41 =1 / (ωL) pk ), ωC 42 =1 / (ωL) sk The parameters of the resonant capacitor with constant voltage characteristics are derived as follows:

[0102]

[0103] This leads to the expression for the system output voltage:

[0104]

[0105] Z eq2 The expression is:

[0106]

[0107] Ultimately, U can be obtained L =nU s , among which, U s U is the input high-frequency AC voltage. L The output DC voltage is rectified, filtered and regulated. The variable gain coefficient n plays a voltage regulation role, indicating that the load side output of the receiver of the single-transmitter secondary dual-parallel pickup type MCR-WPT system has constant voltage characteristics.

[0108] The full-bridge synchronous rectification module includes the fifth switching transistor Q1, the sixth switching transistor Q2, the seventh switching transistor Q3, the eighth switching transistor Q4, and the fourth capacitor C4;

[0109] The fifth switching transistor Q1 is connected in series with the seventh switching transistor Q3, the sixth switching transistor Q2 is connected in series with the eighth switching transistor Q4, the Q1-Q3 series branch and the Q2-Q4 series branch are connected in parallel, and then connected in parallel with C4.

[0110] The full-bridge synchronous rectifier module receives the electrical energy output from the MCR-WPT module 3. By driving Q1, Q2, Q3 and Q4, it rectifies the AC power output from the MCR-WPT module into DC power. C4 filters out noise in the rectified voltage and transmits the filtered DC power to the Boost converter module.

[0111] The BOOST converter module includes inductor L4, ninth switching transistor T1, diode D5, fifth capacitor C5, and load resistor R. L ;

[0112] Fifth capacitor C5 and load resistor R L Parallel, C5-R L The parallel path is connected in series with diode D5, the ninth switching transistor T1 is connected in parallel with diode D5, and the parallel branch of D5-T1 is connected in series with inductor L4.

[0113] The Boost converter module receives DC power from the full-bridge synchronous rectifier module. Because the 12V DC power input from the input module has energy loss after being transmitted through the H-bridge high-frequency inverter module, MCR-WPT module and full-bridge synchronous rectifier module, in order to ensure efficient constant voltage output of the system, the secondary control module controls the on / off state of T1: when T1 is on, L4 stores energy and D5 is off to prevent energy backflow into C5; when T1 is off, L4 releases energy, D5 is on and guides the inductor energy into C5, while C5 smooths the output voltage ripple, and finally transmits the regulated power to the load module.

[0114] The load module includes a load resistor R L ;

[0115] The secondary closed-loop control module includes a secondary ADS1115 chip and a PWM controller;

[0116] The ADS1115 chip and the secondary-side ESP8266 chip are connected in series to form a secondary-side closed-loop control path;

[0117] The secondary closed-loop control module samples R through the secondary ADC1115 chip. L Output voltage / current information and transmit it to, for example Figure 4 The PWM controller shown outputs a control signal to drive the Boost converter module, achieving efficient and stable system output.

[0118] like Figure 2 As shown, L4 is the core energy storage component in the Boost converter module. In the multi-voltage constant output circuit based on a transformer T-network, L4 and the equivalent leakage inductance L of the secondary side leakage flux induced voltage are related. sk Together they form the equivalent inductance L eq This parameter directly affects the dynamic characteristics of the system, and its dynamic characteristic equation needs to be established to analyze the system response;

[0119] For the Boost converter module, ignoring parasitic parameters, the inductor current i L4 With capacitor voltage u C4 The dynamic equation is:

[0120]

[0121] In the formula, u3 is the input voltage of the Boost converter module, d is the duty cycle of T1, and u L For the output voltage of load module 6, the dynamic equation is linearized at the static operating point, and the duty cycle-output voltage transfer function G can be derived through Laplace transform. vd(s) for:

[0122]

[0123] In the formula, U3 is the steady-state value of the input voltage of the Boost converter module. The zero-point frequency of the system in the right half-plane is:

[0124]

[0125] Because the reduction in the zero-point frequency of the right half-plane leads to a loss of phase margin and a decrease in system stability, a dual closed-loop control architecture is designed: first, the inner current loop rapidly adjusts the inductor current to suppress the dynamic hysteresis caused by the equivalent inductance; then, based on the equivalent characteristics of the current loop, the outer voltage loop is designed to achieve steady-state accuracy control of the output voltage. Layered decoupling simplifies the system design. Specifically, the inner current loop uses a PI controller to adjust the inductor current, and its open-loop transfer function G... io(s) for:

[0126]

[0127] In the formula, K p,i For the current loop proportionality coefficient, K i,i For the current loop integral coefficient, U tri This is the carrier amplitude. When the current loop bandwidth ω ci Much larger than the voltage loop bandwidth ω cv And the parameter tuning makes K p,i >>K i,i At that time, the formula for the PI parameter of the inner current loop is:

[0128]

[0129] When ω is satisfied cv <<ω ci When required, the formula for the voltage loop PI parameter is derived:

[0130]

[0131] In addition, leakage inductance L sk The impact will cause U3 fluctuations, according to the Boost steady-state relationship:

[0132]

[0133] Taking the partial derivative of U3, we can obtain the feedforward compensation quantity d. ff for:

[0134]

[0135] Feedforward compensation can compensate for the duty cycle d during the instant of U3 fluctuation. ff It directly cancels out disturbances without waiting for voltage loop feedback adjustment, thereby improving the system's dynamic response speed and preventing voltage fluctuations from being transmitted to the output side;

[0136] In summary, the inner current loop in the PWM controller passes through K p,i To handle the deviation between the current I5 on inductor L4 and the set reference current: I5 is converted into a voltage signal through a sampling resistor, which is then acquired by the secondary-side ADC1115 and compared with the reference current to obtain the deviation, K. p,i By adjusting the PWM duty cycle increment through proportional calculation, the current I5 is made to quickly track the command, suppressing L eq Dynamic hysteresis to reduce dynamic losses; voltage outer loop through K i Eliminate output voltage U L Steady-state error relative to set voltage: U acquired via secondary-side ADC1115 L The steady-state deviation, K, is obtained by comparing it with the sampling reference corresponding to the set value. i By gradually eliminating deviations through integral calculations and locking the set voltage value, the voltage fluctuation problem of the T-type equivalent network is solved. Feedforward compensation blocks input disturbances from the source U3: the change in U3 is sampled, and the feedforward compensation amount is obtained according to the steady-state relationship of the Boost circuit. It is directly superimposed on the duty cycle of the PWM controller output signal to shorten the adjustment time and reduce transition loss. The three work together to achieve stable multi-voltage output and improve system efficiency.

[0137] The wireless transmission module includes a secondary ESP8266 chip and a primary ESP8266 chip;

[0138] The secondary-side ESP8266 chip and the primary-side ESP8266 chip transmit data via WIFI;

[0139] The wireless transmission module will collect the R data from the secondary closed-loop control. L The output information is transmitted from the secondary ESP8266 chip to the primary ESP8266 chip via WIFI. The primary ESP8266 chip then transmits the received information to the primary closed-loop control module, providing feedback for the primary closed-loop control.

[0140] Under the composite strategy of primary-side closed-loop control - transformer equivalent network - secondary-side closed-loop control, the system experimental waveforms demonstrate significant technical advantages: when n=1, the system input-output waveforms are as follows: Figure 5 As shown in (a) and (b), the switching transistors in the H-bridge high-frequency inverter module achieve zero-voltage switching, effectively reducing inverter switching losses; when the system starts up and the load changes abruptly, the output voltage U1 of the H-bridge high-frequency inverter module and the output voltage U of the load module... L The waveform is as follows Figure 5 As shown in (c) and (d), it can be seen that the introduction of feedforward compensation can generate an anticipatory adjustment effect at the moment of disturbance, greatly reduce the dynamic adjustment lag of the PI controller, reduce its dynamic adjustment burden, thereby suppressing the impact of load changes on the system startup speed and ensuring output stability under dynamic operating conditions.

[0141] This embodiment also provides a control method for a high-efficiency, wide-load constant-voltage multi-voltage output MCR-WPT system, including:

[0142] The H-bridge high-frequency inverter module, driven by the primary-side closed-loop control module, inverts DC power into high-frequency AC power for the MCR-WPT module. The MCR-WPT module then regulates the high-frequency AC power and transmits it to the full-bridge synchronous rectifier module. The full-bridge synchronous rectifier module rectifies the AC power and transmits it to the Boost converter module. Under the control signal of the secondary-side closed-loop control module, the Boost converter module stabilizes the voltage and transmits it to the load. The load output information collected by the secondary-side closed-loop control module is transmitted to the primary-side closed-loop control module, ultimately achieving efficient, wide-load, constant-voltage multi-voltage output.

[0143] Specifically, the input module provides 12V DC power to the H-bridge high-frequency inverter module as the input power supply for the MCR-WPT system;

[0144] The primary-side closed-loop control module acquires the output voltage U1 of the H-bridge high-frequency inverter via the ADS1115 chip, and simultaneously receives the secondary-side output voltage U transmitted by the wireless transmission module. L The primary-side closed-loop control module compares the two voltage signals and transmits the comparison information to the STM32 microprocessor. The STM32 microprocessor generates a PWM signal based on the comparison information and transmits the PWM signal to the drive circuit composed of the IR2110 chip. The drive circuit outputs an adapted drive signal to the H-bridge high-frequency inverter module.

[0145] After receiving the drive signal output by the primary-side closed-loop control module, the H-bridge high-frequency inverter module drives its internal S1 and S3, S2 and S4 to conduct alternately, converting the 12V DC power provided by the input module into high-frequency AC power with a frequency of 100kHz and a peak-to-peak value of 24V.

[0146] The MCR-WPT module receives high-frequency AC power from the H-bridge high-frequency inverter circuit. It first filters the input AC power through C1, and then transmits the AC power to L2 and L3 respectively through electromagnetic coupling.

[0147] The specific steps include:

[0148] Step 1: The input module outputs 12V DC power to the H-bridge high-frequency inverter module;

[0149] Step 2: The primary-side closed-loop control module acquires the output voltage of the H-bridge high-frequency inverter module, compares it with the feedback secondary-side output voltage, and transmits the information to the STM32 microprocessor to generate a PWM signal. The PWM signal is driven by the drive circuit to output a drive signal, which enables the H-bridge high-frequency inverter module to invert 12V DC power into 100kHz AC power and input it to the MCR-WPT module.

[0150] Step 3: The MCR-WPT module, based on the transformer T-type equivalent model, adjusts the compensation network capacitance value to regulate the high-frequency AC power to the set voltage and transmits it to the full-bridge synchronous rectification module. The full-bridge synchronous rectification module then rectifies the AC power and transmits it to the Boost converter module.

[0151] Step 4: The Boost converter module achieves efficient voltage regulation under the control of the secondary-side control module, and at the same time feeds back the load output information to the secondary-side control module. The secondary-side control module compares the information with the set value, and then generates a drive signal to control the Boost converter module through the current inner loop, voltage outer loop and feedforward compensation unit.

[0152] Step 5: The secondary-side control module collects the RL output information, which is fed back to the Boost converter module for voltage regulation on the one hand, and sent to the primary-side control module through the wireless transmission module on the other hand. The primary-side control module compares the received information with the set value and generates a drive signal to control the H-bridge high-frequency inverter module, forming a complete closed-loop control, and realizing the system's efficient wide-load constant voltage multi-voltage output.

[0153] Furthermore, the MCR-WPT module includes high-frequency AC voltage regulation, including:

[0154] The equivalent impedance matrix equation is established based on the equivalent model of the transformer T network, and the parameters of the resonant capacitor with constant voltage characteristics are obtained.

[0155] The high-frequency AC voltage is adjusted based on the parameters of the resonant capacitor with constant voltage characteristics.

[0156] The parameters of the resonant capacitor with constant voltage characteristics are as follows:

[0157]

[0158] In the formula, C 41 Here, ω is the compensation capacitor value of the transmitter circuit, ω is the system operating frequency, n is the variable gain coefficient, L1 is the transmitting coil, and M is the value of the transmitter circuit compensation capacitor. 12 For the mutual inductance between the transmitting coil L1 and the first picking coil L2, M 13 For the mutual inductance between the transmitting coil L1 and the second picking coil L3, C 42 The receiving end circuit compensation capacitor value is L2, the first pickup coil is L3, the second pickup coil is M. 23 The first pickup coil L2 and the second pickup coil L3 are mutually inducted.

[0159] At this time, the relationship between the system output voltage and the input voltage is:

[0160] U L =nU s ;

[0161] Where n represents the variable gain coefficient, it can be seen from the above formula that the load side output of the system receiver has constant voltage characteristics, and the MCR-WPT module inputs the transmitted energy to the full-bridge synchronous rectification module.

[0162] After receiving the power output from the MCR-WPT module, the full-bridge synchronous rectifier module rectifies the AC power output from the MCR-WPT module into DC power by driving Q1, Q2, Q3 and Q4; then, C4 filters out the noise in the rectified voltage and transmits the filtered DC power to the Boost converter module.

[0163] Furthermore, the Boost converter module, under the control signal of the secondary-side closed-loop control module, achieves voltage regulation and transmits the voltage to the load, including:

[0164] The secondary-side closed-loop control module samples the voltage / current information output by the load through the secondary-side ADC1115 chip and transmits it to the PWM controller. The PWM controller outputs a control signal to drive the switching of the ninth switching transistor T1 in the Boost converter module.

[0165] When the ninth switching transistor T1 is turned on, the inductor L4 stores energy, and the diode D5 is turned off to prevent the energy from flowing back into the fifth capacitor C5;

[0166] When the ninth switching transistor T1 is turned off, the inductor L4 releases energy, the diode D5 turns on and guides the inductor energy into the fifth capacitor C5. At the same time, the fifth capacitor C5 smooths the output voltage ripple and finally transmits the regulated electrical energy to the load.

[0167] Specifically, the Boost converter module receives DC power from the full-bridge synchronous rectifier module. Because the 12V DC power input from the module experiences energy loss after passing through the H-bridge high-frequency inverter module, MCR-WPT module, and full-bridge synchronous rectifier module, a secondary-side closed-loop control module controls the switching of T1 to ensure efficient constant voltage output. When T1 is on, L4 stores energy, and D5 is off, preventing backflow of energy into C5. When T1 is off, L4 releases energy, and D5 conducts, guiding inductor energy into C5. Simultaneously, C5 smooths the output voltage ripple, ultimately transmitting the regulated DC power to R. L ;

[0168] The secondary closed-loop control module samples R through the secondary ADC1115 chip. L The output voltage / current information is transmitted to the PWM controller, which outputs control signals to drive the Boost converter module to work, achieving efficient and stable output of the system.

[0169] Furthermore, the PWM controller includes: an inner current loop control unit, an outer voltage loop control unit, and a feedforward compensation unit;

[0170] The inner loop control unit adjusts the current loop proportional coefficient K. p,i Integral coefficient K of the current loop i,i Tracking inductor current;

[0171] The voltage outer loop control unit adjusts the voltage loop proportional coefficient K. p Voltage loop integral coefficient K i Eliminate steady-state error of output voltage;

[0172] The feedforward compensation unit uses the feedforward compensation amount d ff To counteract disturbances;

[0173] Among them, the current loop proportionality coefficient K p,i Integral coefficient K of the current loop i,i for:

[0174]

[0175] Voltage loop proportionality coefficient K p Voltage loop integral coefficient K i for:

[0176]

[0177] Feedforward compensation amount d ff for:

[0178]

[0179] Among them, L eq The equivalent leakage inductance L4 is the voltage induced by the leakage flux on the secondary side. sk The equivalent inductance formed by the combination, U tri ω is the carrier amplitude. ci U is the bandwidth of the current loop. L R is the output voltage of the Boost converter module, D is the duty cycle of the PWM controller output, and R is the output voltage of the Boost converter module. L For system load, ω cv U1 is the voltage loop bandwidth, and U2 is the output voltage of the full-bridge synchronous rectifier module.

[0180] The three units mentioned above work together to achieve stable multi-voltage output and improve system efficiency. Simultaneously, the secondary-side control module uses the R signal acquired by the secondary-side ADS1115 chip... L The output information is transmitted to the wireless transmission module;

[0181] Furthermore, the wireless transmission module transmits R through the secondary ESP8266 chip. L The output information is transmitted to the primary-side ESP8266 chip via WIFI, and the primary-side ESP8266 chip then transmits the received information to the primary-side control module.

[0182] The embodiments described above are merely preferred embodiments of the present invention and are not intended to limit the scope of the present invention. Various modifications and improvements made to the technical solutions of the present invention by those skilled in the art without departing from the spirit of the present invention should fall within the protection scope defined by the claims of the present invention.

Claims

1. A high-efficiency, wide-load constant-voltage multi-voltage output MCR-WPT system, characterized in that, Includes: H-bridge high-frequency inverter module, MCR-WPT module, full-bridge synchronous rectification module, Boost converter module, primary-side closed-loop control module, and secondary-side closed-loop control module; The H-bridge high-frequency inverter module is used to output high-frequency AC power to the MCR-WPT module under the drive of the primary-side closed-loop control module. The MCR-WPT module is used to transmit the regulated high-frequency AC power to the full-bridge synchronous rectification module; The full-bridge synchronous rectification module is used to rectify the high-frequency AC power and input it to the Boost converter module; The secondary closed-loop control module is used to output control signals based on load output information; The Boost converter module is used to achieve voltage regulation and transmit it to the load under the control signal of the secondary closed-loop control module. The primary-side closed-loop control module is used to achieve efficient, wide-load constant voltage multi-voltage output of the system based on the load output information.

2. The high-efficiency wide-load constant voltage multi-voltage output MCR-WPT system according to claim 1, characterized in that, The H-bridge high-frequency inverter module includes: a first switching transistor S1, a second switching transistor S2, a third switching transistor S3, and a fourth switching transistor S4; the first switching transistor S1 and the third switching transistor S3 are connected in series, the second switching transistor S2 and the fourth switching transistor S4 are connected in series, and the series branch of the first switching transistor S1 and the third switching transistor S3 is connected in parallel with the series branch of the second switching transistor S2 and the fourth switching transistor S4.

3. The high-efficiency wide-load constant voltage multi-voltage output MCR-WPT system according to claim 1, characterized in that, The MCR-WPT module includes: a transmitting coil L1, a first capacitor C1, an internal resistance R1 of the transmitting coil, a first pickup coil L2, an internal resistance R2 of the first pickup coil, a second capacitor C2, a second pickup coil L3, an internal resistance R3 of the second pickup coil, and a third capacitor C3. Among them, the mutual inductance M between the transmitting coil L1 and the first picking coil L2 is... 12 The mutual inductance M between the first pickup coil L2 and the second pickup coil L3 23 The mutual inductance M between the transmitting coil L1 and the second picking coil L3 13 The transmitting coil L1 is connected in series with the first capacitor C1 and the internal resistance R1 of the transmitting coil; the first pickup coil L2 is connected in series with the internal resistance R2 of the first pickup coil and the second capacitor C2; the second pickup coil L3 is connected in series with the internal resistance R3 of the second pickup coil and the third capacitor C3; and the second capacitor C2 is connected in series with the third capacitor C3.

4. The high-efficiency wide-load constant voltage multi-voltage output MCR-WPT system according to claim 1, characterized in that, The full-bridge synchronous rectification module includes: a fifth switching transistor Q1, a sixth switching transistor Q2, a seventh switching transistor Q3, an eighth switching transistor Q4, and a fourth capacitor C4; the fifth switching transistor Q1 and the seventh switching transistor Q3 are connected in series, the sixth switching transistor Q2 and the eighth switching transistor Q4 are connected in series, the series branch of the fifth switching transistor Q1-the seventh switching transistor Q3 and the series branch of the sixth switching transistor Q2-the eighth switching transistor Q4 are connected in parallel, and then connected in parallel with the fourth capacitor C4.

5. The high-efficiency wide-load constant voltage multi-voltage output MCR-WPT system according to claim 1, characterized in that, The Boost converter module includes: inductor L4, ninth switching transistor T1, diode D5, fifth capacitor C5, and load resistor R. L The fifth capacitor C5 and the load resistor R L Parallel connection, parallel branch C5-R L The ninth switching transistor T1 is connected in parallel with diode D5, and the parallel branch D5-T1 is connected in series with inductor L4.

6. The high-efficiency wide-load constant voltage multi-voltage output MCR-WPT system according to claim 1, characterized in that, The primary-side closed-loop control module includes: a primary-side ADS1115 chip, a data comparator, an STM32 microprocessor, and an IR2110 chip connected in sequence to form a primary-side closed-loop control path. The secondary-side closed-loop control module includes a secondary-side ADS1115 chip and a PWM controller; the ADS1115 chip and the PWM controller are connected in sequence to form a secondary-side closed-loop control path.

7. The control method for a high-efficiency wide-load constant voltage multi-voltage output MCR-WPT system according to claim 1, implemented based on the high-efficiency wide-load constant voltage multi-voltage output MCR-WPT system according to any one of claims 1-6, characterized in that, include: The H-bridge high-frequency inverter module, driven by the primary-side closed-loop control module, inverts DC power into high-frequency AC power for the MCR-WPT module. The MCR-WPT module then regulates the voltage of the high-frequency AC power and transmits it to the full-bridge synchronous rectifier module. The full-bridge synchronous rectifier module rectifies the AC power and transmits it to the Boost converter module. Under the control signal of the secondary-side closed-loop control module, the Boost converter module stabilizes the voltage and transmits it to the load. It then transmits the load output information collected by the secondary-side closed-loop control module to the primary-side closed-loop control module, ultimately achieving efficient, wide-load, constant-voltage multi-voltage output.

8. The control method for a high-efficiency, wide-load constant-voltage multi-voltage output MCR-WPT system according to claim 7, characterized in that, The MCR-WPT module includes the following high-frequency AC voltage regulation: The equivalent impedance matrix equation is established based on the equivalent model of the transformer T network, and the parameters of the resonant capacitor with constant voltage characteristics are obtained. The high-frequency AC voltage is adjusted according to the parameters of the resonant capacitor with constant voltage characteristics. The parameters of the resonant capacitor with constant voltage characteristics are as follows: In the formula, C 41 Here, ω is the compensation capacitor value of the transmitter circuit, ω is the system operating frequency, n is the variable gain coefficient, L1 is the transmitting coil, and M is the value of the transmitter circuit compensation capacitor. 12 For the mutual inductance between the transmitting coil L1 and the first picking coil L2, M 13 For the mutual inductance between the transmitting coil L1 and the second picking coil L3, C 42 The receiving end circuit compensation capacitor value is L2, the first pickup coil is L3, the second pickup coil is M. 23 The first pickup coil L2 and the second pickup coil L3 are mutually inducted.

9. The control method for a high-efficiency, wide-load constant-voltage multi-voltage output MCR-WPT system according to claim 7, characterized in that, The Boost converter module achieves voltage regulation and transmits it to the load under the control signal of the secondary-side closed-loop control module, including: The secondary-side closed-loop control module samples the voltage / current information output by the load through the secondary-side ADC1115 chip and transmits it to the PWM controller. The PWM controller outputs a control signal to drive the switching of the ninth switching transistor T1 in the Boost converter module. When the ninth switching transistor T1 is turned on, the inductor L4 stores energy, and the diode D5 is turned off to prevent the energy from flowing back into the fifth capacitor C5; When the ninth switching transistor T1 is turned off, the inductor L4 releases energy, the diode D5 turns on and guides the inductor energy into the fifth capacitor C5. At the same time, the fifth capacitor C5 smooths the output voltage ripple and finally transmits the regulated electrical energy to the load.

10. The control method for a high-efficiency wide-load constant voltage multi-voltage output MCR-WPT system according to claim 9, characterized in that, The PWM controller includes: an inner current loop control unit, an outer voltage loop control unit, and a feedforward compensation unit; The inner loop control unit adjusts the current loop proportional coefficient K. p,i Integral coefficient K of the current loop i,i To handle current deviations; The voltage outer loop control unit uses the voltage loop integral coefficient K. i Eliminate steady-state error of output voltage; The feedforward compensation unit uses the feedforward compensation amount d ff To counteract disturbances; Wherein, the current loop proportionality coefficient K p,i Integral coefficient K of the current loop i,i for: The voltage loop integral coefficient K i for: The feedforward compensation amount d ff for: Among them, L eq The equivalent leakage inductance L4 is the voltage induced by the leakage flux on the secondary side. sk The equivalent inductance formed by the combination, U tri ω is the carrier amplitude. ci U is the bandwidth of the current loop. L R is the output voltage of the Boost converter module, D is the duty cycle of the PWM controller output, and R is the output voltage of the Boost converter module. L For system load, ω cv K represents the voltage loop bandwidth, ΔU3 is the deviation between the actual value of the input voltage U3 and the set stable reference value of U3, and K is the voltage loop bandwidth. p This is the voltage loop proportionality coefficient.

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