Magnet coil power supply system, control method and electronic equipment

Abstract

The invention relates to the technical field of electronic circuits, in particular to a magnet coil power supply system, a control method and electronic equipment. The magnet coil power supply system comprises a subsystem and a control module. The subsystem comprises a plurality of sub-modules and a magnet coil sub-module; the plurality of sub-modules are arranged in an array in the form of M rows and N columns; the sub-module comprises a first capacitor and a driving module; the first capacitor is connected in parallel with the driving module; the control module is connected with the driving module; the control module is configured to generate M * N groups of driving pulse signals for the plurality of sub-modules by adopting a carrier phase-shifting modulation mode; for the ith row of sub-modules in the array, the corresponding driving pulse signals have the same phase offset relative to the driving pulse signals of the first row of sub-modules, and the offset of the phase offset is (i-1) / M carrier periods. The power supply voltage and the working current of the magnet coil can be greatly improved by arranging the plurality of sub-modules in an array, and current ripples can be reduced and the control efficiency can be improved by a phase shift control strategy.

Description

Technical Field

[0001] This disclosure relates to the field of electronic circuit technology, and in particular to a magnet coil power supply system and method, and electronic equipment. Background Technology

[0002] The fusion magnet power supply consists of toroidal field and poloidal field power supplies. The toroidal field power supply powers the toroidal field coils (TF coils), generating a strong magnetic field to confine and control the high-temperature plasma. The poloidal field power supply powers the poloidal field coils (PF coils), primarily involved in plasma initiation, configuration control, and equilibrium maintenance. As one of the core components of a magnetically confined nuclear fusion device, the magnet coils, through the synergistic effect of the aforementioned magnetic fields, are crucial for achieving controlled thermonuclear reactions.

[0003] Currently, fusion magnet power supplies generally employ AC pulse generator sets in conjunction with thyristor converters to form a power supply system. In this traditional approach, the AC pulse generator set serves as the primary pulse power source. The AC output is rectified by the thyristor converter through phase control, converting it into controlled DC power before supplying it to the magnet coils, thereby establishing the required pulsed magnetic field in the coils.

[0004] However, during the power supply pulse, the generator's rotational speed continuously changes as the stored energy is released. This dynamic process directly leads to a non-constant frequency of the generator's output voltage. For thyristor-triggered systems that rely on grid frequency synchronization, this frequency variation makes it difficult to capture and lock the synchronization signal, thus affecting control accuracy and the waveform quality of the output current. Summary of the Invention

[0005] To address the aforementioned technical problems, this disclosure provides a magnet coil power supply system and control method, as well as an electronic device.

[0006] In a first aspect, this disclosure provides a magnet coil power supply system, which includes a subsystem and a control module. The subsystem includes multiple submodules and a magnet coil submodule. The multiple submodules are arranged in an array of M rows and N columns. M and N are both integers greater than 1. M submodules are connected in series to form a phase module, and N phase modules are connected in parallel. The magnet coil submodule is connected to the N phase modules. The submodule includes a first capacitor and a drive module. The first capacitor is connected in parallel with the drive module. The control module is connected to the drive module. The control module is configured to generate M×N sets of drive pulse signals for the multiple submodules using a carrier phase-shift modulation method. For the i-th row of submodules in the array, the corresponding drive pulse signal has the same phase offset relative to the drive pulse signal of the first row of submodules, and the phase offset is (i-1) / M carrier cycles. 1≤i≤M, and i is an integer. The drive pulse signal is used to control the on / off state of the drive module in the submodule.

[0007] Secondly, this disclosure provides a control method for a magnet coil power supply system, applicable to any magnet coil power supply system as described in the first aspect. A carrier phase-shift modulation method is used to generate M×N sets of drive pulse signals for multiple sub-modules; for the i-th row sub-module in the array, the corresponding drive pulse signal has the same phase offset relative to the drive pulse signal of the first row sub-module, the phase offset being (i-1) / M carrier cycles; 1≤i≤M, and i is an integer; wherein, the drive pulse signal is used to control the on / off state of the drive module in the sub-module.

[0008] Thirdly, this disclosure provides an electronic device, including: a memory for storing a computer program; and a processor for executing the computer program to implement the steps of the control method for any of the above-described magnet coil power supply systems.

[0009] Compared with the prior art, the technical solution provided in this disclosure has the following advantages: By adopting a subsystem architecture with an M-row N-column array, the supply voltage and operating current of the magnet coil can be maximized. Simultaneously, by connecting each column of submodules in series to form a phase module and then driving the magnet coil in parallel, combined with a carrier phase-shift control strategy, the i-th row is phase-shifted for (i-1) / M carrier cycles. This allows the system to significantly increase the equivalent switching frequency of the entire drive system while maintaining a low switching frequency for each submodule, thereby greatly reducing output current ripple and electromagnetic interference, providing the magnet coil with an extremely smooth, stable, and high-precision drive current. Specifically, when each submodule only needs to switch at 1kHz, a 4-row array can produce an equivalent 4kHz drive effect, significantly reducing the output current ripple amplitude, while the electromagnetic interference energy is dispersed to a wider frequency band, resulting in a significant decrease in peak value. Furthermore, the modular architecture allows the system to maintain normal output by bypassing any submodule and readjusting the operating points of the remaining modules when any submodule fails, achieving both high-quality current output and high reliability. Attached Figure Description

[0010] The accompanying drawings, which are incorporated in and form a part of this specification, illustrate embodiments consistent with this disclosure and, together with the description, serve to explain the principles of this disclosure.

[0011] To more clearly illustrate the technical solutions in the embodiments of this disclosure or the prior art, the accompanying drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, for those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0012] Figure 1 A schematic diagram of a magnet coil power supply system provided in an embodiment of this disclosure; Figure 2 A schematic diagram of a submodule provided in an embodiment of this disclosure; Figure 3 A waveform diagram of a magnet coil power supply system provided in an embodiment of this disclosure; Figure 4 A schematic diagram of a current detection module provided in an embodiment of this disclosure; Figure 5 A schematic diagram of a circumferential field magnet coil power supply subsystem provided in an embodiment of this disclosure; Figure 6 A schematic diagram of a poloidal field magnet coil power supply subsystem provided in an embodiment of this disclosure; Figure 7 A schematic diagram of a comparison circuit provided in an embodiment of this disclosure; Figure 8A flowchart of a magnet coil power supply system control method provided in this disclosure embodiment; Figure 9 A flowchart of another magnet coil power supply system control method provided in an embodiment of this disclosure.

[0013] Reference numerals: 10, Subsystem; 11, Toroidal field magnet coil power supply subsystem; 12, Polecular field magnet coil power supply subsystem; 101, Submodule; 111, Toroidal submodule; 121, Polecular submodule; 102, Magnet coil submodule; 112, Toroidal magnet coil submodule; 122, Polecular magnet coil submodule; 103, Phase module; 20, Control module; 21, Comparator circuit; 211, Switching unit; 212, Comparator; 30, Drive module; 31, First drive module; 32, Second drive module; 40, Current detection module; 1, First branch; 2, Second branch; 3, Third branch; 4, Fourth branch; 5, Fifth branch; 6, Sixth branch; Branch circuit; 100, Magnet coil power supply system; C1, First capacitor; D1, First diode; D2, Second diode; D3, Third diode; D4, Fourth diode; D5, Fifth diode; D6, Sixth diode; D7, Seventh diode; D8, Eighth diode; S1, First transistor; S2, Second transistor; S3, Third transistor; S4, Fourth transistor; S5, Fifth transistor; S6, Sixth transistor; N1, First output node; N2, Second output node; N3, Third output node; N4, Fourth output node; R1, First resistor; R2, Second resistor; L1, First coil; L2, Second coil; L3, Third coil. Detailed Implementation

[0014] To better understand the above-mentioned objectives, features, and advantages of this disclosure, the solutions disclosed herein will be further described below. It should be noted that, unless otherwise specified, the embodiments and features described herein can be combined with each other.

[0015] Numerous specific details are set forth in the following description in order to provide a full understanding of this disclosure, but this disclosure may also be implemented in other ways different from those described herein; obviously, the embodiments in the specification are only some, and not all, of the embodiments of this disclosure.

[0016] Currently, fusion magnet power supplies generally employ AC pulse generator sets in conjunction with thyristor converters to form a power supply system. In this traditional approach, the AC pulse generator set serves as the primary pulse power source. The AC output is rectified by the thyristor converter through phase control, converting it into controlled DC power before supplying it to the magnet coils, thereby establishing the required pulsed magnetic field in the coils.

[0017] However, during the power supply pulse, the generator's rotational speed continuously changes as the stored energy is released. This dynamic process directly leads to a non-constant frequency of the generator's output voltage. For thyristor-triggered systems that rely on grid frequency synchronization, this frequency variation makes it difficult to capture and lock the synchronization signal, thus affecting control accuracy and the waveform quality of the output current.

[0018] Secondly, as a semi-controlled device, the thyristor's turn-on and turn-off mechanisms inherently possess a control blind zone: turn-on requires not only a sufficiently strong trigger signal, but turn-off relies even more on the anode current naturally crossing zero or forced commutation by external force. As long as the anode current is higher than the holding current, the device will continue to conduct and cannot be turned off by gate control. This characteristic limits the system's response speed and dynamic adjustment capability, exhibiting control lag and accuracy loss in scenarios requiring rapid cutoff or precise adjustment of the magnetic field to cope with rapid changes in plasma.

[0019] Based on this, such as Figure 1 and Figure 2 As shown, this disclosure provides a schematic diagram of a magnet coil power supply system.

[0020] The magnet coil power supply system 100 includes: a subsystem 10 and a control module 20; the subsystem 10 includes: multiple submodules 101 and a magnet coil submodule 102.

[0021] Multiple submodules 101 are arranged in an array of M rows and N columns; M and N are both integers greater than 1.

[0022] M sub-modules 101 are connected in series to form phase module 103, and N phase modules 103 are connected in parallel; magnet coil sub-module 102 is connected to N phase modules 103; sub-module 101 includes: a first capacitor C1 and a drive module 30; the first capacitor C1 and the drive module 30 are connected in parallel.

[0023] The control module 20 is connected to the drive module 30. The control module 20 is configured to generate M×N sets of drive pulse signals for multiple sub-modules 101 using carrier phase shift modulation. For the i-th row sub-module 101 in the array, the corresponding drive pulse signal has the same phase offset relative to the drive pulse signal of the first row sub-module 101. The phase offset is (i-1) / M carrier cycles, where 1≤i≤M and i is an integer. The drive pulse signal is used to control the on / off state of the drive module 30 in the sub-module 101.

[0024] In some embodiments, the first capacitor C1 is a supercapacitor; a supercapacitor has the characteristics of rapid charging and discharging and high power. The supercapacitor can store energy to subsequently power the magnet coil submodule 102.

[0025] For example, the supercapacitor can be connected to a power source to charge the supercapacitor. After charging, the supercapacitor can act as an energy storage device to store energy and generate high voltage and high current so as to quickly provide drive current to the magnet coil submodule 102.

[0026] For example, multiple sub-modules 101 are arranged in an array of 4 rows and 3 columns, and the switching frequency of a single drive module 30 is 1kHz; that is, M=4, N=3; there are a total of 12 sub-modules 101 in 4 rows and 3 columns. Four sub-modules 101 in the vertical direction (column direction) are connected in series to form a phase module 103. Three such phase modules 103 are connected in parallel to jointly power the magnet coil sub-module 102.

[0027] The control module 20 generates 12 sets of drive pulse signals, whose carrier phases are uniformly allocated row by row. The first row: the phase offset is (1-1) / 4=0, that is, the reference phase is 0°; the second row: the phase offset is (2-1) / 4=1 / 4, that is, a delay of 1 / 4 period, which is 90°; the third row: the phase offset is (3-1) / 4=1 / 2, which is 180°; the fourth row: the phase offset is (4-1) / 4=3 / 4, that is, a delay of 3 / 4 period, which is 270°.

[0028] Reference Figure 3 The first row of submodules 101 has a phase of 0°, and each subsequent row of submodules 101 is delayed by (i-1) / M carrier cycles. Initially, the switching frequency of each drive module 30 remains 1kHz, with the same switching losses as a typical 1kHz system. Because the drive pulses of the four submodules 101 in the same column are sequentially 90° out of phase, the voltage ripples they generate are staggered in time. When these ripples are superimposed in the magnet coil (a large inductor), they cancel each other out.

[0029] For a linearly varying carrier wave, after M-path phase shifting, its equivalent switching frequency can be increased to M times that of a single submodule 101, i.e., equivalent switching frequency = 4 × 1 kHz = 4 kHz. The total current ripple frequency of the driving magnet coil is 4 kHz, and its ripple amplitude is significantly reduced compared to a single 1 kHz driving module 30; this provides an extremely smooth and stable current for the magnet coil submodule 102.

[0030] Furthermore, before phase shifting, all 12 sub-modules 101 switch simultaneously at 1kHz and its harmonics, generating huge concentrated interference with very high electromagnetic interference peaks. After phase shifting, the switching energy is dispersed around 4kHz and its harmonics. Although the total interference energy remains unchanged, its spectrum is broadened, and the interference peak at each specific frequency point is significantly reduced.

[0031] In summary, the technical solution provided by this disclosure, by adopting a subsystem 10 architecture arranged in an M-row N-column array, can maximize the supply voltage and operating current of the magnet coil. At the same time, by connecting each column of sub-modules 101 in series to form a phase module 103 and then driving the magnet coil in parallel, combined with a carrier phase shift control strategy, the i-th row is phase shifted for (i-1) / M carrier cycles, which enables the system to significantly improve the equivalent switching frequency of the entire drive system while maintaining the low switching frequency of each sub-module 101. This greatly reduces the output current ripple and electromagnetic interference, providing the magnet coil with an extremely smooth, stable and high-precision drive current.

[0032] like Figure 4 As shown, the magnet coil power supply system 100 also includes a current detection module 40.

[0033] The current detection module 40 is connected to the sub-module 101; the current detection module 40 is configured to acquire the output current value of each column of sub-module 101.

[0034] The control module 20 is connected to the current detection module 40. The control module 20 is also configured to generate an adjustment command based on the output current value obtained by the current detection module when a fault is detected in the submodule 101 in the i-th row and j-th column.

[0035] The adjustment command is transmitted to the drive module 30 of one or more normally operating sub-modules 101 in column j, so that the total output current of column j is adjusted to be the same as the output current of the other normally operating columns.

[0036] For example, a 4x3 array, i.e., M=4, N=3; the entire array is connected in series to form 3 phase modules 103, which are then connected in parallel to drive a magnet coil sub-module 102.

[0037] If a fault occurs in submodule 101 in row 2, column 1 (i.e., i=2, j=1), the current detection module 40 monitors the output current of each column (i.e., each phase module 103) in real time. Each column has a current sensor that measures the currents I1, I2, and I3 in columns 1, 2, and 3, respectively.

[0038] When control module 20 detects a fault in submodule 101 in row 2, column 1 (e.g., by detecting abnormal voltage, current, or temperature), control module 20 will first bypass the faulty submodule 101, preventing it from participating in energy conversion. Since column 1, i.e., the first phase module 103, has lost a submodule 101, its output voltage capability will decrease. In a parallel structure, the output voltage of each phase module 103 is the same (equal to the load voltage), but the current in each column is determined by the equivalent impedance of each phase module 103 and the load. At this time, because column 1 is missing a submodule 101, its equivalent impedance may change, causing the current I1 in column 1 to be inconsistent with the currents I2 and I3 in the other two columns.

[0039] To maintain load current balance, control module 20 generates adjustment commands to regulate the remaining normal sub-modules 101 in column 1 (i.e., sub-modules 101 in rows 1, 3, and 4 of column 1). The adjustment typically involves modifying the modulation signals of these sub-modules 101, for example, by increasing the duty cycle of drive module 30 to boost the output voltage of column 1. This compensates for the voltage loss caused by the absence of one sub-module 101, enabling column 1 to output the same current as columns 2 and 3.

[0040] The specific adjustment process can be as follows: Control module 20 compares I1, I2, and I3. If it finds that I1 is too small, it increases the modulation amplitude of the normal submodule 101 in the first column (or increases its duty cycle) to increase the total output voltage of the first column, thereby increasing I1 until I1=I2=I3. At the same time, the row-by-row phase shift control strategy is still maintained, that is, the first row does not shift phase, the second row shifts phase by 1 / 4 cycle, i.e., 90°, the third row shifts phase by 2 / 4 cycle, i.e., 180°, and the fourth row shifts phase by 3 / 4 cycle, i.e., 270°. Although the submodule 101 in the second row is faulty in the first column, it still works normally in other columns (the second and third columns). Therefore, the phase shift control of the second row is still maintained, but the submodule 101 in the second row of the first column is bypassed and does not participate in modulation.

[0041] Assuming each normal submodule 101 outputs 100V at its rated duty cycle, a series connection of four submodules 101 in one column can output 400V. When one submodule 101 in the first column fails and is bypassed, the maximum output voltage of the first column drops to 300V. In a parallel circuit, if the load voltage is 300V, the first column can output 300V, but each submodule 101 in the other two columns only needs to output 75V (i.e., 75% duty cycle) to reach 300V. At this point, if the load requires 300V, the first column has reached its limit, while the other two columns still have a margin. However, if we want the current to be balanced across the columns, we need to reduce the overall system output voltage so that the first column can also participate in regulation.

[0042] More likely, the load voltage is determined by the load, and the system adjusts to balance the current in each column. In reality, due to the parallel connection, the output voltages of each phase module 103 are the same, but the currents may differ. The control module 20 adjusts the duty cycle of the first column to make its output voltage consistent with the other columns, while simultaneously adjusting to make the currents in each column equal. However, because the first column has one less module, its equivalent impedance changes, and its current may be lower under the same output voltage. Therefore, the control module 20 needs to increase the duty cycle of the first column to output a higher voltage within the same switching cycle to compensate for the change in its internal impedance, thereby making the current in the first column consistent with the other columns.

[0043] This application achieves precise management and fault response for the sub-module 101 array by introducing a current detection module 40. When the system is running normally, the current detection module 40 continuously monitors the output current of each column. Once a fault is detected in the sub-module 101 of the i-th row and j-th column, the control module 20 immediately generates an adjustment command based on the real-time current data. By increasing the drive duty cycle or modulation depth of the normal sub-module 101 in the j-th column, it actively compensates for the output voltage lost due to the bypassing of the faulty module, so that the total current of the column can be quickly restored to the same level as other columns. This process ensures that the faulty column can still provide the same current as the normal column, thereby maintaining the stability of the overall current of the magnet coil. like Figure 5 As shown, subsystem 10 includes: a toroidal field magnet coil power supply subsystem 11; the toroidal field magnet coil power supply subsystem 11 includes: multiple toroidal submodules 111; the toroidal submodules 111 include: a first capacitor C1 and a first drive module 31.

[0044] The first drive module 31 includes: a first bridge arm and a second bridge arm connected in parallel with the first capacitor C1.

[0045] The first bridge arm includes a first branch 1 and a first diode D1 connected in series. The first branch 1 includes a first transistor S1 and a second diode D2 connected in reverse parallel. The control terminal of the first transistor S1 is connected to the control module 20 and receives the first pulse width modulation control signal issued by the control module 20. The connection point of the first branch 1 and the first diode D1 is the first output node N1.

[0046] The second bridge arm includes a second branch 2 and a third diode D3 connected in series. The second branch 2 includes a second transistor S2 and a fourth diode D4 connected in reverse parallel. The control terminal of the second transistor S2 is connected to the control module 20 and receives the second pulse width modulation control signal issued by the control module 20. The connection point between the second branch 2 and the third diode D3 is the second output node N2.

[0047] In this configuration, the first output node N1 of a first drive module 31 is connected to the second output node N2 of the drive module 30 adjacent in the vertical direction; the sub-module 101 in the vertical direction is connected in series through the first output node N1 and the second output node N2.

[0048] Figure 5 The first drive module 31 is a hybrid bridge, that is, the first output node N1 of the first drive module 31 is connected to the second output node N2 of the second drive module 31, the first output node N1 of the second drive module 31 is connected to the second output node N2 of the third drive module 31, and so on, until the first output node N1 of the last drive module 31 is connected to the magnet coil submodule 102.

[0049] For example, a 4x3 array, i.e., M=4, N=3; the entire array is connected in series to form 3 phase modules 103, which are then connected in parallel to drive a magnet coil sub-module 102.

[0050] The four sub-modules 101 connected in series are controlled by carrier phase-shift PWM. The carrier phase of each module is shifted sequentially by 1 / 4 cycle, which staggers their switching actions in time; each sub-module 101 can output +V or 0 at any given moment. Due to the phase-shift control, there are many possible combinations of level states for the four modules; if the first sub-module 101 outputs +V, the second sub-module 101 outputs 0, the first sub-module 101 outputs +V, and the first sub-module 101 outputs 0, the total output voltage is 2V.

[0051] By precisely controlling four modules that can only output two voltage levels, stepped waves of multiple voltage levels such as 0, 1V, 2V, 3V, and 4V can be synthesized. These stepped waves are close to ideal sine waves with extremely low harmonic content, providing an extremely smooth excitation current for the circumferential field magnet.

[0052] For example, if one of the submodules 101 in one column fails, only three submodules 101 remain in the series link, and the maximum output voltage capability drops from 4V to 3V. In order to continue driving the coil to achieve the required current, the control module 20 will correspondingly increase the modulation depth (duty cycle) of the remaining three normal submodules 101, so that they output +V for more time to compensate for the voltage loss due to the loss of one module.

[0053] like Figure 5 As shown, the toroidal field magnet coil power supply subsystem 11 also includes a toroidal magnet coil submodule 112.

[0054] The first end of the circumferential magnet coil submodule 112 is connected to the second output node N2 of the first circumferential submodule 111 in each column; the second end of the circumferential magnet coil submodule 112 is connected to the first output node N1 of the last circumferential submodule 111 in each column.

[0055] The circumferential magnet coil submodule 112 includes: a first resistor R1 and a first coil L1.

[0056] The first end of the first resistor R1 is the first end of the circumferential magnet coil submodule 112, and the second end of the first resistor R1 is connected to the first end of the first coil L1; the first end of the first coil L1 is the second end of the circumferential magnet coil submodule 112.

[0057] The first coil L1 is used to generate a circumferential magnetic field, and the first inductor has a smoothing effect on the current. Combined with the multi-level voltage waveform generated by the submodule 101, an extremely smooth coil current can be obtained. The voltage across the first coil L1 is V1=I1*R1+L1*di / dt. The first resistor R1 can determine the required basic voltage I1*R1.

[0058] For example, if it is necessary to increase the coil current from one stable value to another higher stable value, the specific process is as follows: The control module 20 calculates the voltage required to achieve the target current. Through phase-shifted PWM control, the four sub-modules 101 work together to synthesize the required voltage waveform. This voltage is applied to the series circuit of the circumferential magnet coil sub-module 112. The coil current I1 begins to rise exponentially, and its rate of increase is determined by the time constant τ = L1 / R1. The current detection module 40 continuously monitors I1 and feeds the data back to the control module 20. The control module 20 adjusts the PWM signals of each sub-module 101 in real time based on the feedback to ensure that I1 accurately and smoothly tracks the predetermined trajectory without overshoot or oscillation.

[0059] like Figure 6 As shown, subsystem 10 includes: a poloidal field magnet coil power supply subsystem 12; the poloidal field magnet coil power supply subsystem 12 includes: multiple poloidal submodules 121; the poloidal submodule 121 includes: a first capacitor C1 and a second drive module 32.

[0060] The second drive module 32 includes a third bridge arm and a fourth bridge arm connected in parallel with the first capacitor C1.

[0061] The third bridge arm includes a third branch 3 and a fourth branch 4 connected in series. The third branch 3 includes a third transistor S3 and a fifth diode D5 connected in anti-parallel. The control terminal of the third transistor S3 is connected to the control module 20 and receives the third pulse width modulation control signal issued by the control module 20. The fourth branch 4 includes a fourth transistor S4 and a sixth diode D6 connected in anti-parallel. The control terminal of the fourth transistor S4 is electrically connected to the control module 20 and receives the fourth pulse width modulation control signal issued by the control module 20. The connection point of the third branch 3 and the fourth branch 4 is the third output node N3.

[0062] The fourth bridge arm includes a fifth branch 5 and a sixth branch 6 connected in series. The fifth branch 5 includes a fifth transistor S5 and a seventh diode D7 connected in anti-parallel. The control terminal of the fifth transistor S5 is connected to the control module 20 and receives the fifth pulse width modulation control signal issued by the control module 20. The sixth branch 6 includes a sixth transistor S6 and an eighth diode D8 connected in anti-parallel. The control terminal of the sixth transistor S6 is electrically connected to the control module 20 and receives the sixth pulse width modulation control signal issued by the control module 20. The connection point between the fifth branch 5 and the sixth branch 6 is the fourth output node N4.

[0063] Among them, the third output node N3 of a second drive module 32 is connected to the fourth output node N4 of the second drive module 32 adjacent in the vertical direction; multiple polar sub-modules 121 in the vertical direction are connected in series through the third output node N3 and the fourth output node N4.

[0064] Figure 6 The first drive module 31 is a fully controlled H-bridge, meaning that the first output node N1 of the first drive module 31 is connected to the second output node N2 of the second drive module 31, the first output node N1 of the second drive module 31 is connected to the second output node N2 of the third drive module 31, and so on, until the first output node N1 of the last drive module 31 is connected to the magnet coil submodule 102.

[0065] For example, a 4x3 array, i.e., M=4, N=3; the entire array is connected in series to form 3 phase modules 103, which are then connected in parallel to drive a magnet coil sub-module 102.

[0066] The four sub-modules 101 connected in series employ carrier phase-shift PWM control. The carrier phase of each module is shifted sequentially by 1 / 4 cycle, which staggers their switching actions in time. Each sub-module 101 can output +V, -V, or 0 at any given moment. Since each sub-module 101 can output both positive and negative levels, the four modules connected in series can synthesize an output voltage level ranging from -4V to +4V, with a greater number of steps, thus synthesizing an approximately sine wave with positive and negative symmetry and extremely low harmonic content. This makes the current driving the poloidal field coil very smooth and stable even during rapid changes, avoiding plasma disturbances caused by current ripple.

[0067] A fully controlled H-bridge allows current and voltage to be in the same or opposite directions. This means the system can act as a power source to supply energy to a magnet, or as a load to absorb the enormous magnetic energy stored in the magnet and feed it back to charge the supercapacitor.

[0068] For example, if a rapid increase in forward current is required, the control module 20 commands all (or most) submodules 101 to output +V, with a total voltage of 4V, and the coil current rapidly increases in the positive direction.

[0069] For example, if it is necessary to maintain the current, the control module 20 adjusts the PWM so that the total voltage is equal to the voltage drop across the resistor of the magnet coil submodule 102, at which time the current remains stable.

[0070] For example, if a rapid reduction in current or reversal is required, the control module 20 can command the submodule 101 to output a negative voltage.

[0071] like Figure 6 As shown, the poloidal field magnet coil power supply subsystem 12 also includes: a poloidal magnet coil submodule 122.

[0072] The first end of the polar magnet coil submodule 122 is connected to the fourth output node N4 of the first polar submodule 121 in each column; the second end of the polar magnet coil submodule 122 is connected to the third output node N3 of the last polar submodule 121 in each column.

[0073] The polar magnet coil submodule 122 includes: a second resistor R2 and a second coil L2.

[0074] The first end of the second resistor R2 is the first end of the polar magnet coil submodule 122, and the second end of the second resistor R2 is connected to the first end of the second coil L2.

[0075] The first end of the second coil L2 is the second end of the polar magnet coil submodule 122.

[0076] The second coil L2 is used to generate a poloidal magnetic field, and the second inductor has a smoothing effect on the current. Combined with the multi-level voltage waveform generated by the submodule 101, an extremely smooth coil current can be obtained. The voltage across the second coil L2 is V2=I2*R2+L2*di / dt. The second resistor R2 can determine the required basic voltage I2*R2.

[0077] For example, if it is necessary to increase the coil current from one stable value to another higher stable value, the specific process is as follows: The control module 20 calculates the voltage required to achieve the target current. Through phase-shifted PWM control, the four sub-modules 101 work together to synthesize the required voltage waveform. This voltage is applied to the series circuit of the pole magnet coil sub-module 122. The coil current I2 begins to rise exponentially, and its rate of increase is determined by the time constant τ = L2 / R2. The current detection module 40 continuously monitors I2 and feeds the data back to the control module 20. The control module 20 adjusts the PWM signals of each sub-module 101 in real time based on the feedback to ensure that I2 accurately and smoothly tracks the predetermined trajectory without overshoot or oscillation.

[0078] In summary, during plasma discharge, the toroidal field magnet coil power supply subsystem 11 typically produces a unidirectional and highly stable toroidal field current. Therefore, a low-cost hybrid H-bridge, namely the first drive module 31, can be used to generate stable unidirectional current and voltage. However, for the poloidal field magnet coil power supply subsystem 12, the current must change rapidly and frequently in both directions to achieve plasma shaping, positioning, and control. Therefore, a fully controlled H-bridge, namely the second drive module 32, can be used, providing the ability to output negative voltage and realizing bidirectional energy flow, thus meeting the requirements of poloidal field control for speed, accuracy, and flexibility.

[0079] In some embodiments, the magnet coil power supply system 100 includes a plurality of subsystems 10, including both a circumferential field magnet coil power supply subsystem 11 and a poloidal field magnet coil power supply subsystem 12; the control module 20 can switch the corresponding subsystem 10 to supply power according to the actual situation.

[0080] It should be noted that in some embodiments, the first transistor S1 can be an insulated gate bipolar transistor (IGBT), and the second transistor S2, the third transistor S3, the fourth transistor S4, the fifth transistor S5, and the sixth transistor S6 can all be IGBTs.

[0081] Based on this, firstly, the transistors in both the first drive module 31 and the second drive module 32 are IGBT fully controllable power devices, offering a wide operating range and high power utilization. Furthermore, the IGBTs utilize PWM control to achieve high-frequency switching (kHz level), and PWM modulation can rapidly adjust the output voltage to adapt to the rapid current changes in the circumferential or poloidal field coils. Simultaneously, the IGBTs can be actively controlled to turn off via PWM, enabling bidirectional energy flow and achieving high efficiency. Finally, the PWM control of the IGBTs can distribute switching losses and provides short-circuit protection, making them more suitable for the high reliability requirements of the device.

[0082] Furthermore, each diode is connected in antiparallel to its corresponding transistor, allowing the diodes to provide freewheeling current to the magnet coil submodule 102. When a sudden change occurs in the current of submodule 101, the freewheeling diode (the diode connected in antiparallel to the transistor) can make the current on the load unit change more smoothly, preventing sudden voltage changes across the magnet coil submodule 102 that could damage it.

[0083] like Figure 5 and Figure 6 As shown, it also includes: multiple third coils L3.

[0084] The first end of a third coil L3 is connected to the first end of a phase module 103, and the second end of a third coil L3 is connected to the first end of a magnet coil submodule 102.

[0085] The first end of a phase module 103 is connected to the second end of a magnet coil submodule 102.

[0086] For example, there are 3 phase modules 103. Each phase module 103 is composed of 4 sub-modules 101 connected in series. The 3 third coils L3 are connected to the 3 phase modules 103 one by one.

[0087] For example, if a stable current of 6000A is required to provide the magnet coil submodule 102, the control module 20 can control each of the three phase modules 103 to output 2000A. In this way, the load of each submodule 101 is the same, which is beneficial to thermal management and extends service life.

[0088] Alternatively, one phase module 103 may output 1500A due to device aging or temperature difference, while the other two phase modules 103 may each output 2250A.

[0089] At this time, the third coil L3 is equivalent to a coupling inductor, which can make the current ripple output by the phase module 103 instantaneously consistent, so that the phase module 103 can work independently and stably, realizing the function of dynamic decoupling.

[0090] Meanwhile, if a serious fault such as a short circuit occurs inside a phase module 103, a huge fault current will surge from the other phase modules 103 and the magnet coil sub-module 102 to the faulty phase module 103. The third coil L3 can greatly limit the rise rate and peak value of this fault current and prevent the fault from spreading.

[0091] like Figure 7 As shown, the control module 20 includes: a comparison circuit 21; the comparison circuit 21 includes: a comparator 212 and a switching unit 211.

[0092] The input terminal of comparator 212 is connected to the first terminal of phase module 103 to receive the current of the first terminal of phase module 103, and the reference terminal of comparator 212 is used to receive the reference current; the output terminal of comparator 212 is connected to the control terminal of switch unit 211.

[0093] The first end of the switching unit 211 is used to receive the drive pulse signal and control the drive module 30 to turn on; the second end of the switching unit 211 is used to receive the turn-off signal and control the drive module 30 to turn off; the output end of the switching unit 211 is used to connect to the drive module 30.

[0094] Comparator 212 is configured to compare whether the current value of phase module 103 is greater than the current value of reference current; if yes, it outputs a first voltage signal to the control terminal of switch unit 211; if no, it outputs a second voltage signal to the control terminal of switch unit 211.

[0095] The switching unit 211 is configured to connect the second terminal to the output terminal when it receives the first voltage signal, and to connect the first terminal to the output terminal when it receives the second voltage signal.

[0096] For example, phase module 103 is composed of 4 sub-modules 101 connected in series, and the reference current is set to 2500A. 2500A is a threshold that requires a fast response; the first voltage signal is a low-level signal "0", and the second voltage signal is a high-level signal "1".

[0097] If the phase module 103 is working normally, the output current value is 2000A. The comparator 212 compares the current of the phase module 103 2000A with the reference current 2500A. Since 2000A < 2500A, the comparator 212 outputs a second voltage signal to connect the first terminal of the switching unit 211 to the output terminal.

[0098] The switching unit 211 can be understood as a single-pole double-throw switch controlled by the level output of comparator 212. Upon receiving a high level, it connects the first terminal's normal drive pulse signal to the output terminal. The normal PWM wave is then transmitted to the transistor control terminal of the drive module 30, enabling normal operation.

[0099] If phase module 103 malfunctions, the current will suddenly rise to 2600A. Since 2600A > 2500A, comparator 212 outputs a first voltage signal, connecting the second terminal of switching unit 211 to the output terminal, cutting off the connection with the normal drive pulse signal. As a result, a constant turn-off signal (0V) is sent to drive module 30, forcing all IGBTs in phase module 103 to turn off immediately. Through comparator circuit 21, the system can be protected more quickly to prevent damage.

[0100] In summary, by cascading multiple sub-modules 101, the supply voltage and operating current of the magnet coil sub-module 102 can be maximized. Simultaneously, by connecting each column of sub-modules 101 in series to form a phase module 103, which is then connected in parallel to drive the magnet coil, and combining this with a carrier phase-shift control strategy, the i-th row is phase-shifted for (i-1) / M carrier cycles. This allows the system to significantly increase the equivalent switching frequency of the entire drive system while maintaining a low switching frequency for each sub-module 101, thereby substantially reducing output current ripple and electromagnetic interference. Furthermore, the use of IGBTs reduces voltage dynamic response time and improves dynamic control performance. For the circumferential field, hybrid power devices are used to reduce costs; for the poloidal field, fully controllable power devices are used, resulting in a wide power supply operating range and high power utilization. Finally, the total current is used for current feedback, ensuring consistent control signals for each phase and providing overcurrent protection. The control method is simple, highly stable, and includes fault detection, further extending the lifespan of the devices.

[0101] like Figure 8 and Figure 9 As shown, this disclosure also provides a control method for a magnet coil power supply system, which is applied to the aforementioned magnet coil power supply system.

[0102] like Figure 8 As shown, the control methods include: S1. Use carrier phase-shift modulation to generate M×N sets of drive pulse signals for multiple sub-modules.

[0103] S2. For the i-th row submodule in the array, the corresponding driving pulse signal has the same phase offset as the driving pulse signal of the first row submodule, and the phase offset is (i-1) / M carrier cycles.

[0104] Where 1≤i≤M, and i is an integer; the drive pulse signal is used to control the on / off state of the drive module in the submodule.

[0105] The control method provided in this disclosure generates row-phase-shifted drive pulses (the i-th row is phase-shifted by (i-1) / M carrier cycles) for the M×N array of sub-modules. This allows each sub-module to maintain its original low switching frequency while increasing the system's equivalent switching frequency to M times that of a single sub-module through the interleaving and superposition of its output ripples on the time axis. This significantly reduces output current ripple and electromagnetic interference peaks. Furthermore, the modular approach lays the foundation for efficient fault-tolerant control and current sharing management, ultimately providing an extremely smooth, stable, and high-precision drive current for the magnet coil.

[0106] like Figure 9 As shown, the control method also includes: S101. Obtain the output current value of each column of sub-modules.

[0107] S102. When a fault is detected in the submodule of row i and column j, an adjustment command is generated based on the output current value obtained by the current detection module.

[0108] S103. The adjustment command is transmitted to the drive module of one or more normally operating sub-modules in column j, so that the total output current of column j is adjusted to be the same as the output current of the other normally operating columns.

[0109] This control method monitors the output current of each column in real time. When a fault is detected in the submodule of row i, column j, an adjustment command is immediately generated to the normally functioning submodule in that column, dynamically increasing its output capability to compensate for the fault loss. For example, in a 4×3 submodule array, when a submodule fails and is bypassed, the system can, within milliseconds, increase the duty cycle of the remaining normal submodules in that column, rapidly restoring its total output current to the same level as other columns. This ensures that the total current of the magnet coil remains stable, achieving fault-tolerant operation under fault conditions and greatly improving system reliability.

[0110] This disclosure also provides an electronic device, including: a memory for storing a computer program; and a processor for executing the computer program to implement the steps of the control method for any of the above-described magnet coil power supply systems.

[0111] The electronic device executes the computer program stored in the memory through its processor, realizing the complete digital integration of the above-mentioned magnet coil drive control method; it can flexibly configure phase shift parameters, adjust PWM strategy in real time and quickly execute fault-tolerant control through software algorithms, which not only significantly improves the system's adaptability and control accuracy to different operating conditions, but also greatly reduces the complexity and cost of later maintenance and functional optimization.

[0112] It should be noted that, in this document, relational terms such as "first" and "second" are used merely to distinguish one entity or operation from another, and do not necessarily require or imply any such actual relationship or order between these entities or operations. Furthermore, the term "comprising" or any other variations thereof is intended to cover non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements includes not only those elements but also other elements not expressly listed, or elements inherent to such a process, method, article, or apparatus. Without further limitations, an element defined by the phrase "comprising one..." does not exclude the presence of other identical elements in the process, method, article, or apparatus that includes said element.

[0113] The above description is merely a specific embodiment of this disclosure, enabling those skilled in the art to understand or implement it. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the general principles defined herein may be implemented in other embodiments without departing from the spirit or scope of this disclosure. Therefore, this disclosure is not to be limited to the embodiments described herein, but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

Claims

1. A magnet coil power supply system, characterized in that, include: Subsystems and control modules; The subsystem includes: multiple sub-modules and a magnet coil sub-module; the multiple sub-modules are arranged in an array of M rows and N columns; M and N are both integers greater than 1; M sub-modules are connected in series to form a phase module, and N phase modules are connected in parallel; the magnet coil sub-module is connected to the N phase modules; The submodule includes: a first capacitor and a driving module; the first capacitor is connected in parallel with the driving module. The control module is connected to the drive module; the control module is configured to generate M×N sets of drive pulse signals for the multiple sub-modules using carrier phase shift modulation; for the i-th row sub-module in the array, the corresponding drive pulse signal has the same phase offset relative to the drive pulse signal of the first row sub-module, and the phase offset is (i-1) / M carrier cycles; 1≤i≤M, and i is an integer; The drive pulse signal is used to control the on / off state of the drive module in the submodule.

2. The magnet coil power supply system according to claim 1, characterized in that, Also includes: Current detection module; The current detection module is connected to the sub-module; The current detection module is configured to acquire the output current value of each column of the sub-modules; The control module is connected to the current detection module, and the control module is further configured to: when a fault is detected in the submodule of the i-th row and j-th column, generate an adjustment command based on the output current value obtained by the current detection module; The adjustment command is transmitted to the drive module of one or more normally functioning sub-modules in column j, so that the total output current of column j is adjusted to be the same as the output current of the other normally functioning columns.

3. The magnet coil power supply system according to claim 1 or 2, characterized in that, The subsystem includes: a toroidal field magnet coil power supply subsystem; the toroidal field magnet coil power supply subsystem includes: multiple toroidal sub-modules; the toroidal sub-modules include: a first capacitor and a first drive module; The first drive module includes: a first bridge arm and a second bridge arm connected in parallel with the first capacitor; The first bridge arm includes a first branch and a first diode connected in series. The first branch includes a first transistor and a second diode connected in reverse parallel. The control terminal of the first transistor is connected to the control module and receives a first pulse width modulation control signal from the control module. The connection point of the first branch and the first diode is the first output node. The second bridge arm includes a second branch and a third diode connected in series. The second branch includes a second transistor and a fourth diode connected in reverse parallel. The control terminal of the second transistor is connected to the control module and receives a second pulse width modulation control signal from the control module. The connection point between the second branch and the third diode is the second output node. In this configuration, the first output node of one of the first driving modules is connected to the second output node of the adjacent driving module; the sub-modules along the vertical direction are connected in series through the first output node and the second output node.

4. The magnet coil power supply system according to claim 3, characterized in that, The circumferential field magnet coil power supply subsystem also includes: a circumferential magnet coil submodule; The first end of the circumferential magnet coil submodule is connected to the second output node of the first circumferential submodule in each column; the second end of the circumferential magnet coil submodule is connected to the first output node of the last circumferential submodule in each column. The circumferential magnet coil submodule includes: a first resistor and a first coil; The first end of the first resistor is the first end of the circumferential magnet coil submodule, and the second end of the first resistor is connected to the first end of the first coil. The first end of the first coil is the second end of the circumferential magnet coil submodule.

5. The magnet coil power supply system according to claim 1 or 2, characterized in that, The subsystem includes: a poloidal field magnet coil power supply subsystem; the poloidal field magnet coil power supply subsystem includes: multiple poloidal sub-modules; the poloidal sub-modules include: a first capacitor and a second driving module; The second drive module includes a third bridge arm and a fourth bridge arm connected in parallel with the first capacitor; The third bridge arm includes a third branch and a fourth branch connected in series. The third branch includes a third transistor and a fifth diode connected in anti-parallel. The control terminal of the third transistor is connected to the control module and receives a third pulse width modulation control signal from the control module. The fourth branch includes a fourth transistor and a sixth diode connected in anti-parallel. The control terminal of the fourth transistor is electrically connected to the control module and receives a fourth pulse width modulation control signal from the control module. The connection point of the third branch and the fourth branch is the third output node. The fourth bridge arm includes a fifth branch and a sixth branch connected in series. The fifth branch includes a fifth transistor and a seventh diode connected in anti-parallel. The control terminal of the fifth transistor is connected to the control module and receives a fifth pulse width modulation control signal from the control module. The sixth branch includes a sixth transistor and an eighth diode connected in anti-parallel. The control terminal of the sixth transistor is electrically connected to the control module and receives a sixth pulse width modulation control signal from the control module. The connection point between the fifth branch and the sixth branch is the fourth output node. In this configuration, the third output node of one of the second driving modules is connected to the fourth output node of the adjacent second driving module along the vertical direction; and multiple polar sub-modules along the vertical direction are connected in series through the third output node and the fourth output node.

6. The magnet coil power supply system according to claim 5, characterized in that, The poloidal field magnet coil power supply subsystem further includes: a poloidal magnet coil submodule; The first end of the pole magnet coil submodule is connected to the fourth output node of the first pole submodule in each column; the second end of the pole magnet coil submodule is connected to the third output node of the last pole submodule in each column. The polar magnet coil submodule includes: a second resistor and a second coil; The first end of the second resistor is the first end of the pole magnet coil submodule, and the second end of the second resistor is connected to the first end of the second coil. The first end of the second coil is the second end of the pole magnet coil submodule.

7. The magnet coil power supply system according to claim 1, characterized in that, Also includes: Multiple third coils; A first end of one of the third coils is connected to a first end of one of the phase modules, and a second end of one of the third coils is connected to a first end of the magnet coil submodule; The first end of one of the phase modules is connected to the second end of the magnet coil submodule.

8. The magnet coil power supply system according to claim 7, characterized in that, The control module includes: a comparison circuit; the comparison circuit includes: a comparator and a switching unit; The input terminal of the comparator is connected to the first terminal of the phase module to receive the current at the first terminal of the phase module; the reference terminal of the comparator is used to receive a reference current; the output terminal of the comparator is connected to the control terminal of the switching unit. The first terminal of the switching unit is used to receive a drive pulse signal to control the drive module to turn on; the second terminal of the switching unit is used to receive a turn-off signal to control the drive module to turn off; the output terminal of the switching unit is used to connect to the drive module. The comparator is configured to compare whether the current value of the phase module current is greater than the current value of the reference current; if yes, it outputs a first voltage signal to the control terminal of the switching unit; if no, it outputs a second voltage signal to the control terminal of the switching unit. The switching unit is configured to connect the second terminal to the output terminal when receiving the first voltage signal, and to connect the first terminal to the output terminal when receiving the second voltage signal.

9. A control method for a magnet coil power supply system, applied to the magnet coil power supply system as described in any one of claims 1 to 8, characterized in that, include: A carrier phase-shift modulation method is used to generate M×N sets of drive pulse signals for multiple sub-modules; For the i-th row submodule in the array, the corresponding driving pulse signal has the same phase offset relative to the driving pulse signal of the first row submodule, and the phase offset is (i-1) / M carrier cycles; 1≤i≤M, and i is an integer; The drive pulse signal is used to control the on / off state of the drive module in the submodule.

10. An electronic device, characterized in that, include: Memory, used to store computer programs; A processor, configured to implement the steps of the control method for the magnet coil power supply system as described in claim 9 when executing the computer program.

Images