Method for regulating the operating current of an LED lighting unit

Abstract

Method for the regulated supply of a consumer (11) with electrical energy by means of a control circuit (10) comprising the steps • Feeding a first output current (I3) into a first terminal (5) of the load (11) by means of a first controllable current source (IS3), which is part of the control circuit (10) and is connected on the other side with its second terminal at low resistance to a supply line (1, 2), via a first terminal of this current source (IS3) and • simultaneous injection of a second output current (I4) by a second adjustable current source (IS4), which is part of the control circuit (10), into a second output (4) of the control circuit (10) and from there into an external resistor (R4), which is not part of the control circuit (10), and from there into the said first terminal (5) of the load (11) by means of the series connection of the independent second adjustable current source (IS4) and the second external electrical resistor (R4), • wherein a first terminal of the second adjustable current source (IS4) is connected to the second output (4) of the control circuit (10) and • wherein the second adjustable power source (IS4) is connected with its second terminal on the other side to the said supply line (1, 2) at low resistance, and • Control of the first output current (I3) and the second output current (I4) by a controller (RG) depending on a measurement parameter (I)3_4 , U I_ist_b ) in such a way that with increasing operating voltage (U) b ) • in a first operating voltage range (A) with a specific magnitude, only the first controllable current source (IS3) delivers a non-zero output current (IS3) and • then in a second operating voltage range (B) immediately adjacent to the first operating voltage range (A) in terms of magnitude, with reference to the operating voltage (U) b ) the second current source (IS4) supplies a non-zero second output current (I4) which increases in magnitude with increasing operating voltage, and the first output current (I3) of the first current source (IS3) is increased by the amount of the value of this second output current (I4) with increasing operating voltage (U). b ) is progressively reduced in amount and • then in an amount proportional to the second operating voltage range (B) relative to the operating voltage (U)b ) immediately adjacent third operating voltage range (C) the second current source (IS4) one from the operating voltage (U b ) provides a second output current (I4) that is independent in magnitude and non-zero, and the first output current (I3) of the first current source (IS3) is negligible in magnitude, but at least less than 1% of the magnitude of the second output current (I4), is characterized by - that by regulating the current, the location where the power loss occurs due to the regulation of the current is also determined by a further control parameter, • that the current magnitude distribution of the sum of the output currents (I3+I4) from the first output current (I3) and the second output current (I4) to the first output current (I3) and the second output current (I4) of the control circuit (10) is determined by at least one control parameter, i.e. a distribution parameter (V) p), is dependent on the control circuit (10) which is determined in the control circuit or specified from the outside via an analog or digital interface (ST) or another signal (PWM).

Description

Introduction and State of the Art

[0001] Many applications require a regulated electrical power supply. In particular, the regulation of the power supply to LED lights in vehicles must meet specific requirements. LED stands for light-emitting diode.

[0002] The LEDs to be powered are usually connected in series, less often in parallel, and are typically supplied by a power source. This regulated power source is fed from an energy source, typically the electrical system of a vehicle.

[0003] The problem here is that regulating the current source leads to a significant power loss within the current source circuit. This has the consequence that, in the case of monolithic integration in the form of an integrated circuit (IC), additional IC areas become necessary to prevent exceeding the critical temperature for the respective semiconductor. At the same time, special cooling measures may be required within the current source housing.

[0004] A typical example of such a device is shown in publication US 2009 / 0033243 A1 in its Fig. 3. Three LEDs are driven by separate current sources. Since the transistors are not fully driven, a relatively high power loss occurs. It is also known from the prior art to limit the current through the LEDs using series resistors. Fig. 2 of US 2009 / 0033243 A1) This reduces the energy efficiency at full power.

[0005] In the device known from US 2013 / 0049597, an LED array is operated with a current-limiting resistor composed of several partial resistors connected in series. Taps driven by switching transistors can shorten the resistance by bypassing partial resistors. The current through the arrangement is measured via a shunt resistor. One advantage of the device according to US 2013 / 0049597 A1 is that the resistors can be placed outside the control circuit and do not necessarily heat it up. However, for a linear regulator, it is advantageous to be able to assume intermediate values. Therefore, this circuit does not solve the problem.

[0006] From DE 10 2007 001 716 A1, an LED control device is known in which a series circuit of LED pairs is supplied by means of two current sources. Another LED is connected between one of the current sources and the series circuit of LED pairs.

[0007] From DE 10 2010 005 907 A1, an LED control device is known which uses an I 2 It is controlled via the C-Bus interface or via a PWM interface.

[0008] From JP S60-107372 A, a device for supplying electrical loads (reference numeral 5 of JP S60-107372 A) is known, in which the power loss in the LED driver (reference numeral 6 of JP S60-107372 A) is reduced by switching off the voltage source (transistor T1 of JP S60-107372 A) at times when the LEDs are not supposed to be emitting light. This does not solve the problem of the large supply voltage range in an automobile and thus the large power drop when driving the LEDs via a current source.

[0009] From EP 2 416 623 A2, a circuit is known in which the current through an LED string is regulated. In this circuit, a bypass current is routed around the LED string via an external resistor (reference 430 of EP 2 416 623 A2). This does not solve the problem of the large supply voltage range in an automobile and thus the large power drop when driving the LEDs via a current source. From EP 2 196 887 A1, a circuit with two transistor current sources connected in parallel (references T1 and T2 of EP 2 196 887 A1) is known. This does not solve the problem of the large supply voltage range in an automobile and thus the large power drop when driving the LEDs via a current source.

[0010] From EP 1 454 511 B1, a circuit is known with a first current source (reference symbol I_P of EP 1 454 511 B1) and a second current source (reference symbol I_D of EP 1 454 511 B1). The first current source (reference symbol I_P of EP 1 454 511 B1) drives a first terminal of the LED (reference symbol D of EP 1 454 511 B1). The second current source (reference symbol I_D of EP 1 454 511 B1) drives a second terminal of the LED (reference symbol D of EP 1 454 511 B1). The first current source (reference number I_P of EP 1 454 511 B1) and the second current source (reference number I_D of EP 1 454 511 B1) are part of a common control circuit (reference number St of EP 1 454 511 B1). This does not solve the problem of the large supply voltage range in an automobile and thus the large power drop when driving the LEDs via a single current source.

[0011] From DE 103 59 196 A1, a device is known in which a current source (reference 2 and RP of DE 103 59 196 A1) connected in parallel to the LED (reference numeral 1 of DE 103 59 196 A1) ensures that the control signal (reference numeral I) S (DE 103 59 196 A1) remains within a predefined value range, so that the control remains within its operating range. This does not solve the problem of the large supply voltage range in an automobile and thus the large power drop when driving the LEDs via a current source through that current source.

[0012] From DE 101 59 765 A1, a device is known in which several switchable current sources (reference numerals I1, I2, I3, I4 of DE 101 59 765 A1) supply current to different nodes of a series circuit of LEDs. This does not solve the problem of the large supply voltage range in an automobile and thus the large power drop when driving the LEDs via a single current source.

[0013] From DE 10 2007 001 716 A1, a light-emitting diode (LED) circuit arrangement is known in which a controlled current source is arranged in series with several series-connected groups of parallel branches. The first group contains a branch with an LED and a branch without an LED. Object of the invention

[0014] The object of the invention is to minimize the power loss to the power source itself resulting from the regulation of the LED current by the supplying power source, in order to significantly reduce the required IC area and the housing complexity of such a control circuit. This object is achieved by means of a device according to claim 1. Description of the basic invention

[0015] The basic idea of ​​the invention is not only to regulate the current, but also to determine the location where the power loss occurs due to the regulation of the current and to define this location of the additional power loss by means of a further control parameter.

[0016] The invention is based on the understanding that a transistor, which is essentially the regulating transistor of a current source, can be considered, in the broadest sense, as an adjustable resistor. If this transistor has a medium resistance value, a maximum amount of power is dissipated through the transistor.

[0017] Within the scope of the invention, it was recognized that an operating range can therefore be defined in which this transistor can be replaced by a second transistor with an external resistor connected downstream. This second transistor then regulates the current, with some of the control power dissipated not in the second transistor itself, but in the external resistor. Thus, the integrated circuit heats up less, since the heating power is generated outside the package in the aforementioned external resistor. If a current is required that reduces the transistor resistance below the sum of the on-resistance (RDS(on)) and the on-resistance (RDS(on)), the following applies: on) of the second transistor and the external resistor, so the first transistor takes over the regulation again.

[0018] This rather simple principle can be generalized in that the current within two current paths is regulated by two parameters such that the sum of the currents in the two current paths correlates with a first parameter, and the distribution of power loss is linked to a second, additional parameter. This is the basic idea of ​​the invention.

[0019] Of course, this principle can also be applied to more than two current paths. In that case, control between the current paths can be performed in both two and multiple dimensions.

[0020] For simplicity, the following describes the supply of a single consumer using two power sources feeding into two current paths. An expert will easily be able to extend this basic concept to three or more current paths.

[0021] This is a device for the regulated supply of electrical energy to at least one load (11) by means of a control circuit (10). For the sake of simplicity, it is assumed that the control circuit (10) has at least four terminals (1, 2, 3, 4). One terminal (2) is, for example, the ground terminal and the reference potential of the control circuit (10) according to the invention, which is part of the device according to the invention. An exemplary load (11) has two supply terminals (5, 6). The terminals (5, 6) of the load (11) are connected to an output (3) and the ground terminal (2) of the control circuit (10). The control circuit (10) is supplied with electrical energy from a regulated or unregulated energy source (7) at least via its supply voltage terminal (1) and the ground terminal (2).The second output of the control circuit (4) is also electrically connected to the aforementioned first terminal (5) of the load (11) via a second external resistor (R4), which, for example, represents a significant difference from the device known from US 2009 / 0033243 A1. The load (11) can also be almost any electrical network of several loads that are part of the load (11). For example, it can be, in part or in whole, a series and / or parallel connection of LEDs. The only important thing is that the power supply to at least part of the load is provided via terminals (5, 6).

[0022] In any case, the load (11) must have a common reference potential (2) with the control circuit (10) and the power source (7). This connection can be direct electrically or indirect via another load or load network. In principle, any type of load with a complex internal resistance, including motors, etc., is suitable. However, this disclosure focuses on LEDs as loads without limiting the generality of this disclosure. For example, the second terminal (6) of the load (11) can be directly connected to the ground terminal (2) of the control circuit (10). Of course, it is possible that the connection between the first output (3) of the control circuit (10) and the first terminal of the load (5) is made via a first external resistor (R3) instead of a direct connection.For the inventive concept to be valid, it is only essential that this first external resistance (R3) has a different value than the second external resistance (R4), since only then is it possible to control the location of the control power loss to a certain extent. Naturally, it is sensible and practical if one of the external resistances (R3, R4) has a value of zero ohms, which in reality corresponds to a very small value other than zero. Typically, such a connection is simply implemented as a direct connection, which corresponds, for example, to a resistance of a few milliohms.

[0023] The resistances (R3, R4) can be considered unequal if, depending on the material of the resistors, they differ from each other by more than 1%, or preferably more than 2%, or preferably more than 5%, or preferably more than 10%, or preferably more than 25%, or preferably more than 50%, or preferably more than 100%. Particularly preferred are lead resistances between the first output (3) of the control circuit (10) and the second terminal of the load (6) of less than 10 ohms, or preferably less than 5 ohms, or preferably less than 2 ohms, or preferably less than 1 ohm, or preferably less than 100 mOhms. Such low resistances can generally be considered, for the purposes of this disclosure, to have a value of almost zero ohms. The load (11) is then supplied with the sum of the two output currents (I3 + I4) via its first terminal (5).In order for the control circuit (10) to perform its core task, namely regulating the current through the load (11), it is obvious that the sum of the output currents (I3+I4) at the outputs (3, 4) of the control circuit (10) must be regulated. This sum of the output currents (I3+I4) must therefore be represented as an actual value within the control circuit. This actual value (I3+I4) is then compared with a setpoint (I.) within the control circuit. sum The specified value is compared to the output current (I3, I4). Both currents (I3, I4) are then adjusted if there are deviations between the sum of the output currents (I3+I4) and the setpoint (I). sum ) adjusted accordingly. In the simplest case, this "corresponding" adjustment is achieved, for example, by a proportional control, in which the two currents (I3, I4) of the two outputs (3, 4) are adjusted by the same factor. This corresponds to the setpoint (I). sumThe function relative to the given total flow (I3+I4) can, of course, also include more complex functions than the simple affine mapping described above. It is important that this function is at least temporarily represented by a bijective, strictly monotonically increasing function between the setpoint (I) and the target value (I). soll ) and the sum of the currents (I3+I4). The second essential controllable parameter is the distribution of the sum current (I3+I4) across the output currents (I3, I4). Since their sum (I3+I4) is determined by the aforementioned setpoint (I) sum ) or a corresponding setpoint is specified, only the ratio of the distribution between these flows (I3, I4) is determined by at least one control parameter. This is referred to below as the distribution parameter (V). p ). This distribution parameter (V p) can be determined from various perspectives. In the simplest case, it is specified externally via an interface. For example, this can be done via a data interface (ST) and another register, or via a PWM interface, where the duty cycle, for example, determines the distribution parameter (V). p ) or one of the aforementioned analogous values ​​(I ref_ext ) is represented. However, determining the distribution parameter (V) is significantly better. p ) within the control circuit (10) itself. For this purpose, the control circuit typically has a suitable component that determines the distribution parameter (V). p ) carries out.

[0024] To determine this distribution parameter (V) p To determine the operating parameters, it is first useful to record the essential operating parameters of the control circuit (10). This recording does not necessarily have to be continuous.

[0025] The setpoint (Isum ) can be specified externally or in the control circuit (10) as an internal reference current (I) ref_int ) are fixed. Of course, it is possible, for example, to convert these quantities into other parameters such as voltages using analog or digital circuits before comparison. This aforementioned specification of the setpoint (I) sum ) can be externally controlled, for example, by a reference current (I) ref_ext ) or a reference resistor (R ref ) or a reference voltage (U I_soll ) can be set. For example, with a programmed specification, a value can be written to a register via a data interface (ST), whereupon a digital-to-analog converter (ADC) generates the setpoint. Numerous methods for this are known in the art, so further explanation is unnecessary here.

[0026] Predetermined time points can be specified for certain operating parameters. Measurements can be performed cyclically or using a band-limited measurement trigger signal. A measurement is triggered when the signal meets certain conditions, such as a zero crossing. The latter method has the advantage of potentially allowing compliance with electromagnetic compatibility requirements. However, this depends on the specific application. Particularly useful measurements include the output current (I3, I4) of the control circuit (10), the output voltage (U3, U4) of the control circuit (10), the output power (P3, P4) of the control circuit (10), and the operating temperature (T).The latter can be measured, for example, in the control circuit (10) itself and / or in parts of the control circuit (10) and / or near the control circuit (10) and / or near a resistor (R3, R4) and / or near a load (11). One or more of these values ​​can then be used to calculate the distribution parameter (V) by analog and / or digital means. p ) are transformed. Of course, a multidimensional control system that regulates both the total current (I3+I4) and the current distribution between the output currents (I3, I4) is advantageous, since the measurements allow for the detection of faulty states, which can, for example, lead to the control circuit being switched off by disconnecting one or more outputs (3, 4). Therefore, it is useful to monitor not only the current values ​​of these measured values, but also their past values ​​and past values ​​for the setpoint of the total current (I3+I4). sum) and the distribution parameter (V p ) for calculating the current target values ​​for the total current (I sum ) and the distribution parameter (V p These past values ​​are used. They may be temporarily stored in a suitable analog or digital memory. This analog memory could, for example, be a low-pass filter or a sample-and-hold circuit.

[0027] All these measured parameters, as well as the course of the stored values, their simple and higher derivatives over time, and the values ​​derived from them, can each be compared with target values.

[0028] The device therefore includes a component, typically a controller (RC), that compares one of the measured values, a stored measured value, or a value derived from it, with a corresponding setpoint. The controller (RC) performs this comparison by checking whether the measured value is less than or greater than the setpoint. Of course, in some cases, it makes sense for the controller to check whether the measured value is equal to a setpoint. This means that the measured value must lie within a tolerance band around the setpoint. It is therefore more accurately described as a target band. Naturally, it is then not useful to simultaneously evaluate these measured values ​​as greater or less than the setpoint.Measured values ​​for such a comparison could include, for example, one of the output currents (I3, I4, I3) or one of the output voltages (U3, U4, U8) or one of the output powers (P3, P4, P8) or the sum of all or part of the output currents (I3+I4, I3+I4+I8) or the sum of all or part of the output powers (P3+P4, P3+P4+P8) or the operating voltage (U) provided by the energy source (7). b) or the temperature (T) of the control circuit (10) or the temperature (T) of a part of the control circuit (10) or the temperature (T) near the control circuit (10) or the temperature (T) near at least one consumer (11) or the temperature (T) near at least one external resistor (R3, R4, R8) or the temperature (T) in a coolant or cooling medium near a resistor (R3, R4, R8) or a stored value of these values ​​or a quantity derived from these values ​​and / or their stored values.

[0029] It has been shown that good results are already achieved if the distribution parameter (V) p ) the operating voltage (U b ) is or correlated with it. However, it is equally conceivable to use it as a distribution parameter (V). p) one of the output currents (I3, I4) or one of the output voltages (U3, U4) or one of the output powers (P3, P4) or the sum of all or part of the output currents (I3+I4) or the sum of all or part of the output powers (P3+P4) or the temperature (T) of the control circuit (10) or the temperature (T) of a part of the control circuit (10) or the temperature (T) near the control circuit (10) or the temperature (T) near a load (11) or the temperature (T) near a resistor (R3, R4) or the temperature (T) of a coolant or cooling medium near a resistor (R3, R4).

[0030] Furthermore, it is also possible to calculate the sum of the output currents (I3+I4) as a function of one of the output voltages (U3, U4), or as a function of one of the output powers (P3, P4), or as a function of the sum of the output powers (P3+P4), or as a function of the to control the temperature (T) of the control circuit (10), or the temperature (T) of a part of the control circuit (10), or the temperature (T) near the control circuit (10), or the temperature (T) near a load (11), or the temperature (T) near a resistor (R3, R4). Instead of the aforementioned values, stored values ​​of these values ​​and / or quantities derived from these values, or the operating voltage (U), can also be used as substitutes or in addition. b ) to be used for the regulation.

[0031] A short-circuit indicator can be an output voltage (U3, U4) that is lower than a predefined setpoint at at least one of the outputs (3, 4) of the control circuit (10). In the case of a power supply for an LED string, this setpoint depends on the number of LEDs. It could, for example, be 0.5V, 0.1V, or 1.5V, but other values ​​are also possible. Incidentally, in the case of an LED circuit, it is advantageous if at least one of the resistors (R3, R4) has a value of zero ohms or close to zero ohms. This should be interpreted as meaning that it should have a value of less than 10 ohms, or preferably less than 5 ohms, or preferably less than 2 ohms, or preferably less than 1 ohm, or preferably less than 100 mOhms.

[0032] If such an error is detected externally by means of signaling or measurement or by deviation from a setpoint or setpoint range or a predetermined time course or course range of one of the previously discussed parameters and / or one of the previously described control variables and / or a quantity derived from them by a component of the control circuit (10), one possible measure that an optional control within the control circuit (10) can take is to reduce or stop the energy supply to at least one consumer (11) in the form of the energy supplied to it by the control circuit (10).

[0033] A special form of self-diagnosis for the device according to the invention can be achieved by disconnecting one of the current branches, for example, the second terminal (4) of the control circuit (10), from the power supply and measuring the voltage across this branch, in this example the second output voltage (U4). This allows the state of an LED string acting as a load (11) to be determined more reliably. However, such a measurement constitutes a disruption of operation. Therefore, this measurement, if performed at all, can only be carried out temporarily and typically only at certain minimum intervals, for example, periodically. Consequently, any possible self-diagnosis in the form of fault detection, at least for one potential fault, can only be performed at specific times and not continuously.

[0034] The control characteristic of a preferred embodiment of the invention for the power supply of LEDs is now such that it depends on the operating voltage (U). b ) has several operating voltage ranges. For the following explanations, it is assumed for simplicity that the first resistor (R3) has a value of zero ohms. If there are multiple branches, one resistor should have a value of zero. In the first operating voltage range (A), the light-emitting diodes (LEDs) are not yet switched on. Therefore, in this operating voltage range, the current through the LEDs and thus the power output increases depending on the operating voltage (U). b ) on. In this operating voltage range, the target current (I) is controlled by the control circuit. sumThe total current (I3+I4) is not yet delivered to the LEDs (11) because it is limited not by the control circuit (10) but by the LEDs, i.e., the load (11). During the transition from operating voltage range A to a second operating voltage range B, the first output (3) supplies the entire current. In this example, the first output (3) is directly connected to the load (11). The output current (I4) of the second output (4), which is connected to the load (11) via the second external resistor (R4), is still open-circuit (OA) at this operating voltage point. The first output (3) must therefore supply the entire total current (I3+I4) because a voltage drop across the second external resistor (R4) at the second output (4) is undesirable.With the transition to the second operating voltage range (B), the regulator of the first current source (IS3) at the first output (3) would have to reduce its internal conductance, which is in parallel with the current source (IS3), in order to avoid having to supply more current. This would lead to an increasing power loss in this regulator. Therefore, the second output (4) now gradually takes over a portion of the total current (I3+I4). This is achieved, for example, by keeping the first output voltage (U3) at the first output (3) of the control circuit (10), and thus the voltage drop across the LEDs and therefore the load (11), constant. This means that the current (I3+I4) through the LEDs remains constant.For this purpose, the second output current (I4) from the second output (4) is adjusted so that the additional voltage drops across the second external resistor (R4), which is connected between the second output (4) and the LEDs, i.e., the second terminal of the load (6). Therefore, in this operating voltage range B, the second resistance power dissipation (P) increases. R4 ) of the second external resistor (R4) increases parabolically, while the LED power dissipation (P LED The current released in the LEDs remains constant. From a certain point onward, the current source (IS4) of the second output (4) no longer supplies enough current (I4) to maintain the voltage across the second external resistor (R4) as the operating voltage (U) continues to increase. b ) to increase further. This point marks the transition to another operating voltage range C, in which both the second resistance power loss (P) R4) in the second external resistor (R4) as well as the LED power loss (P LED The voltage in the LEDs remains almost constant. The additional power loss must now be dissipated within the control circuit (10) itself, which is only possible up to a further operating voltage point. Then, a transition to a fourth operating voltage range (D) occurs, in which the overall power must be reduced to prevent damage to the control circuit (10) and / or the LEDs, i.e., the load (11). In this fourth operating voltage range (D), the load (11) or all loads typically no longer function correctly or completely.

[0035] If more than two outputs are used to supply a consumer (11), here an LED string, more complex area patterns are of course conceivable.

[0036] In the second and third operating voltage ranges (B) and (C), the sum of the output currents (I3+I4) is kept constant. In the second operating voltage range (B), the output current (I4) of the second output (4) is used for adjustment, while in the third operating voltage range (C), the voltage drop across the control circuit (10) adjusts the total current (I3+I4) through the load (11) and keeps it constant. The fourth operating voltage range (D) is typically outside the specifications for the control circuit (10) and therefore only needs to provide emergency operation capabilities. Of course, it is conceivable to use several such control circuits (10), for example, for RGB lighting control. This would require, for instance, three LED strips in the colors red, green, and blue.In this exemplary embodiment, each of these LED strings is supplied with energy by a device according to the invention. For setting the correct color, it is therefore advantageous to combine this triple control circuit with a color sensor (MF). This sensor provides three actual values ​​with which the respective current sums I. sum_r , I sum_g and I sum_b They can be readjusted. Three values ​​can then be specified as external setpoints, which, depending on the color model used, are converted into the setpoints by a computer. sum_r , I sum_g and I sum_b can be converted. Of course, direct specification of the target values ​​via an external circuit and / or by means of programming is also conceivable. Such an external circuit can, for example, be implemented using reference currents (I ref_ext_1 , I ref_ext_2 , I ref_ext_3 ) which are carried out via external resistances (R ref_1 , R ref_2 , R ref_3 ) be imprinted.

[0037] As already mentioned, the available measured values ​​offer the possibility of using them for fault detection. Therefore, a device according to the invention not only has components for performing these measurements and deriving the aforementioned control signals (I) from them. soll , V p ) to generate, but preferably, but not necessarily, also via one that has the function of fault monitoring. This outputs at least one fault signal (S stat ) which can signal an error. Such an error signal (S stat The value can also be the content of a register or a bit that can be read via a digital interface, e.g., a data interface (ST), and whose value is generated by the component in question. Analog signaling via dedicated lines is, of course, also possible.

[0038] Of particular importance is that this component should also be able to receive error messages from other systems that are not part of the control circuit. Thus, the component should preferably be able to be chained with the error signal of another device according to the invention or another device not according to the invention. This allows, for example, a fault in one module, consisting of the control circuit and loads, to shut down all modules connected by chaining. It is particularly advantageous if this chaining is implemented, for example, by means of a wired-OR circuit and a pull-up resistor for the error signal (S). stat ) happens.

[0039] Error modes that should be detected with particular priority include: a) an “open fault”, in which an interruption or significant restriction of the current flow by a consumer is detected, and b) a short circuit in which a consumer is bridged or has a massively reduced internal resistance.

[0040] One characteristic of an "open error" can be, for example, an output current (I3, I4) that is less than 10%, 20%, 30%, 40%, or 50% of a specified target or expected value. A value of less than 30% has proven particularly advantageous.

[0041] Finally, it should be mentioned that with a suitable design of the respective external resistor (R3, R4, R) 4_1 , R 4_2 , R 4_3 , R8) makes it possible to allow operating temperatures far exceeding those permitted for semiconductors, thus enabling the implementation of the control circuit (10) according to the invention as an integrated circuit. The external resistor (R3, R4, R) can also be used. 4_1 , R 4_2 , R 4_3, R8) can be mounted at a different location than the control circuit (10). This allows, for example, suitable thermal insulation between external resistors (R3, R4, R8) and R8. 4_1 , R 4_2 , R 4_3 , R8) and control circuit (10) to protect these from excessive temperature load. The resistor thus acts as a kind of electrical cooler for the system, which makes the nature of the invention particularly clear. It is therefore a feature of a corresponding embodiment of the invention that an external resistor (R3, R4, R8, R) is used. 4_1 , R 4_2 , R 4_3 ) is mounted at such a spatial distance from the control circuit (10) or is otherwise thermally insulated, so that when the maximum intended operating temperature (T) is reached R ) of the relevant external resistance (R3, R4, R8, R 4_1 , R 4_2 , R 4_3) the temperature of the control circuit (10) is increased by no more than 10°C in the best case, or by no more than 20°C in the best case, or by no more than 40°C in the best case, or by no more than 80°C in the best case.

[0042] On the other hand, cooling is particularly effective when the temperature difference between the external resistor and its cooling system, for example a coolant or a heat sink, is maximized. This can be achieved by maximizing the operating temperature of the external resistor. It is therefore a feature of an embodiment of the invention if an external resistor (R3, R4, R8, R) 4_1 , R 4_2 , R 4_3 ) in a specification-compliant operating state of the control circuit (10) a temperature of (T R) of greater than 150°C or better, greater than 200°C or better, greater than 250°C or better, greater than 350°C or better, greater than 450°C. In this context, it is conceivable, for example, to achieve cooling using liquid metal, such as lead or tin, etc. The heat of fusion can also be utilized if the loads are only short-term. The device is therefore capable of successfully controlling very large peak loads, which significantly distinguishes it from the state of the art. Figures Fig. 1 Exemplary basic structure of a device (10) according to the invention with a single LED chain (11) as a consumer. Fig. 2 Exemplary basic structure of a device according to the invention (10) made of Fig. 1 with a single LED string (11) as the load and an additional first resistor R3. Fig. 3 Exemplary basic structure of a control circuit according to the invention (10) made up of Fig. 1 with a single LED chain (11) as a consumer and now three control channels and three power sources (IS3, IS4, IS8). Fig. 4 Exemplary basic structure of a device according to the invention with three LED chains (11_1, 11_2, 11_3) as consumers and three control circuits according to the invention (10_1, 10_2, 10_3) and a fault detection (FD), a color sensor (MF) and a color controller (FR) Fig. Figure 5 shows the exemplary change in the current source and total currents with a change in the operating voltage (U). b ) Fig. Figure 6 shows the exemplary change in power conversion in the LED, the control circuit (10) and in the resistor R4 with a change in the operating voltage (U). b ) Fig. Figure 7 shows the exemplary change in power conversion in the LED, the control circuit (10) and in the resistor R4 with a change in the operating voltage (U). b ) with three power sources. Fig. Figure 8 shows a simplified minimal version of the Fig. 1 with a total flow control of the distribution factor. Fig. Figure 9 shows an exemplary implementation of the system of Fig. 1 with a common current measuring device and no other measuring devices based on a differential amplifier. Fig. Figure 10 shows a simplified minimal version of the Fig. 1 with a sum current control of two parallel current sources (IS3, IS4). Fig. Figure 11 shows an exemplary implementation of the system of Fig. 1 with a common current measuring device based on two independent current sources (TR 3b , TR 4b ). Fig. Figure 12 shows an exemplary implementation of the system of Fig. 1 with a common current measuring device (R mb ) based on two independent power sources (TR 3b , TR 4b ) with specific design of the offset voltage source (V3, V4), Fig. Figure 13 shows a generalization of the Fig. 12 as a half-bridge, where the current sources can also supply negative currents. Fig. Figure 14 shows a generalization of the Fig. 13 as a full or H-bridge, whereby both connections of a complex load are driven through a half-bridge each. Fig. 15 shows a generalization of the Fig. 14, wherein the consumer is connected to a device according to the invention with both supply voltage connections accordingly Fig. 1 is connected, which are controlled via a common controller (RG). Fig. Figure 16 shows the control of a three-phase load using the example of a star-connected stator of an exemplary BLDC motor with three corresponding controls. Fig. 9 per stator coil. The use of half-bridges accordingly. Fig. 13 makes sense. Fig. Figure 17 shows the exemplary change in the current source and total currents with a change in the operating voltage (U). b ), if, under a very high current load, a small portion of the current is additionally supplied by the first current source (IS3) in a fifth operating voltage range (E), which is determined by the Fig. 5 differs. Fig. Figure 18 shows the exemplary change in power conversion in the LED, the control circuit (10) and in the resistor R4 with a change in the operating voltage (U). b), if, under a very high current load, a small portion of the current is additionally supplied by the first current source (IS3) in a fifth operating voltage range (E), which is determined by the Fig. 5 differs. Fig. 19 corresponds Fig. 1 with an inductive load and two freewheeling diodes instead of an LED load. Fig. 20 corresponds Fig. 3 with an inductive load and two freewheeling diodes instead of an LED load. Fig. 21 corresponds Fig. 4 each with an inductive load and two freewheeling diodes instead of an LED load. The ground point could, for example, be the star point of a three-phase motor. Fig. 22 corresponds Fig. 1 with a capacitive load instead of an LED load. Fig. 23 corresponds Fig. 2 with a capacitive load instead of an LED load. Fig. 24 corresponds Fig. 3 with a capacitive load instead of an LED load. Fig. 25 corresponds Fig. 4 each with a capacitive load instead of an LED load. Fig. 26 corresponds Fig. 11 with a regulation via a voltage measurement. Fig. 27 corresponds to a combination of Fig. 11 and Fig. 26 with a regulation on performance measurement. Character description

[0043] The following figures show only some possible configurations of a device according to the invention. The possibilities of the invention become apparent from the preceding and following descriptions and the claims as a whole, as well as the cited documents, which are part of this disclosure.

[0044] Fig. Figure 1 shows an exemplary control circuit (10) according to the invention. It has two outputs (3, 4) and, for each of these outputs (3, 4), an associated current source (IS3, IS4) which is controlled by a controller (RG). The first output current (I3) of the first current source (IS3) is fed directly into the first terminal (5) of the load (11), an LED string. The second output current (I4) of the second current source (IS4) is fed through the resistor (R4) and generates a voltage drop there. The output voltages (U3, U4) are detected by measuring devices (MU3, MU4) and supplied to the controller RG as measured values. Likewise, the first and second output currents (I3, I4) are detected by two further measuring devices (MI3, MI4) and also supplied to the controller (RG) as measured values. The power outputs (P3, P4) are recorded by power measuring devices (MP3, MP4) and fed to the controller (RG) as measured values.

[0045] Likewise, the operating voltage (U)b ) by a measuring device (MU b ) is recorded and supplied to the controller (RG) as a measured value. Not all of these measured values ​​are required for successful implementation. Here, only the potential of the device according to the invention is to be presented. A temperature measuring device (MT) measures the temperature (T) and makes it available to the controller (RG). The controller (RG) controls the device using these measured values ​​and, if necessary, with the help of externally received control inputs, in this case a setpoint (I). soll ), as well as the current sources (IS3, IS4) with any stored and / or derived quantities.

[0046] Fig. 2: Here, in contrast to Fig. 1 Another first external resistor (R3) is shown.

[0047] Fig. 3, in contrast to Fig. 1. A further, third output (8) is provided, which is also connected to the first output (5) via a third external resistor R8. The associated measuring devices (MU8, MI8, MP8) also supply the respective measured values ​​(P8, U8, I8) to the controller (RG) that controls the current sources as a whole. Typically, the third external resistor (R8) is chosen to have twice the value of the second external resistor (R4). It should be noted here that in the further text of this disclosure, the third output will also be referred to as the first output of a further structure. Fig. 1 will be used.

[0048] Fig. Figure 4 shows an exemplary control circuit for RGB LED lighting. The control circuits according to the invention (10_1, 10_2, 10_3) each control an LED string (11_1, 11_2, 11_3) of one color. The second connections (4_1, 4_2, 4_3) are each connected via an external resistor (R). 4_1 , R 4_2 , R4_3 ) is connected to the first terminal (5_1, 5_2, 5_3) of the respective LED string (11_1, 11_2, 11_3). The respective first terminals (3_1, 3_2, 3_3) are directly connected to these. The second terminals (6_1, 6_2, 6_3) of the LED strings (11_1, 11_2, 11_3) are connected to the ground terminal (2) of the device (10). A reference generator (RefG) makes it possible to determine the setpoint values ​​(e.g., I). soll ) of the individual sub-devices (10_1, 10_2, 10_3) from externally by means of the currents (I ref_ext_1 , I ref_ext_2 , I ref_ext_3 ) to adjust these currents. These currents can be adjusted via the resistors (R). ref_1 , R ref_2 , R ref_3 The voltage can be set instead of the current. A controller (CTR) controls the entire device. This can be addressed via a data interface (ST). The example device has a power supply (SUP) that provides the unregulated operating voltage (U). b) for use in the control circuit (10). A color controller (FR) receives information from a color sensor (MF) about the color composition and intensity of the emitted light. This information is converted by the color controller (FR) into setpoint values ​​for the sub-devices (10_1, 10_2, 10_3). This sets a color composition and illumination intensity that meets a specified requirement. Of course, it is also possible to measure the reflected light and adjust the illumination accordingly. For example, the setpoint values ​​of different setpoint sources described above can be multiplied together in a suitable device, typically the controller (RG), to form a common setpoint value (I). sum ) for the respective total flow (I3+I4, I3+I4,+I8) and / or the distribution parameter (V p ) can be combined.

[0049] A fault detection system compares the measured values ​​of the measuring instruments of the sub-devices (10_1, 10_2, 10_3) with target values ​​or target ranges. Past and derived values ​​can also be used. If the fault detector (FD) detects a fault condition, this is indicated by a fault signal (S). stat Output is displayed. Output via the data interface (ST) is also possible. An internal reference (intRef) is used to set basic internal parameters.

[0050] Fig. Figure 5 shows an idealized output current / operating voltage characteristic with a vanishing first external resistance (R3) in a system accordingly Fig. 1. In the first operating voltage range (A), the first output current (I3) at the first output (3) of the control circuit (10) initially rises sharply as the LEDs (11) become conductive, until the control behavior of the regulator (RG) limits this current at the boundary to the second operating voltage range (B). In the second operating voltage range (B), the first output current (I3) decreases with a further increase in the operating voltage (U). bSimultaneously, the second output current (I4) at the second output (4) of the control circuit (10) increases and eventually takes over the total current (I3+I4), which is kept constant, completely at the boundary of the third operating voltage range (C). At the boundary of the third operating voltage range (C), the first output current (I3) is then preferably zero. If the regulator of the second current source (IS4) is then fully open, this means that no power is consumed in the first current source (IS3) at this boundary, since it is switched off, and the power consumption in the second current source is zero because its current regulator has a low resistance and is fully switched on, and the voltage drop occurs entirely across the second external resistor (R4).As the operating voltage continues to increase, the second output current (I4) initially remains constant, but the power loss in the second current source (IS4) then increases, since the second current source (IS4) now has to supply the additional voltage of the operating voltage (U. b ) must be reduced. This continues until the load limit is reached at the boundary of the fourth operating voltage range (D), and a forced reduction of the second output current (I4) with malfunction of the supplied load (11) then begins an emergency running range, which, with further increase, typically ends with the destruction and / or damage of the device, which, however, in the Fig. 5 is no longer shown.

[0051] Fig. Figure 6 shows the distribution of power consumption according to Fig. 5 in the various operating voltage ranges for a device similar to the Fig. 1. In a start-up phase, the first operating voltage range (A), the LEDs (11) do not yet conduct fully and limit the total current (I3+I4). In this first operating voltage range (A), typically only the first output (3) supplies the current for operating the load (11), the LEDs.

[0052] In the second operating voltage range (B), the current is gradually taken over by the second current branch at the second terminal (4) with the second external resistor (R4). The second external resistance power dissipation (P) R4 The power dissipation (P) of the LED, which is converted in the second external resistor (R4), increases parabolically. LED The voltage converted in the LEDs (11) remains largely constant. Above a certain operating voltage point, the second output (4) can no longer supply sufficient voltage. Therefore, the total current (I3+I4) through the LEDs (11) and thus the LED power dissipation (P) would now be LED) increase again. Therefore, the additional power loss is now converted in a third operating voltage range (C) in the control circuit (10). The power loss of the control circuit (P 10 ) now increases continuously. The power consumption of the LEDs (P LED ) remains constant. The power consumption (P) R4 The resistance of the second external resistor R4 remains constant. In a fourth operating voltage range (D), the control can no longer be maintained and the system enters a predetermined emergency running mode.

[0053] Fig. Figure 7 shows the exemplary change in power conversion in the LED, the control circuit (10) and in the second external resistor R4 with a change in the operating voltage (U). b ) with three power sources (IS3, IS4, IS8) accordingly Fig. 3.

[0054] Fig. Figure 8 shows a simple schematic simplification of the Fig. 1 for a simplified implementation. A total current measuring device (MI) 3_4 ) measures the sum (I3+I4) of the output currents (I3, I4). This sum current measuring device (MI) 3_4 ) thus replaces the first current measuring device (MI3) of the Fig. 1 and the second current measuring device (MI4) of the Fig. 1 and summarizes these. It provides an actual value for the total current (I3+I4) to the controller (RG). The controller (RG) controls the total current source (IS) based on this. 3_4 ), which supplies a total current (I3+I4). A controllable current divider (TR3 / TR4) now distributes this preset total current (I3+I4) to the two output currents (I3, I4) depending on a control signal (U). ref2 or I soll )

[0055] Fig. Figure 9 shows a simple exemplary implementation of a device according to the Fig. 8. The exemplary device of the Fig. 9 did not have a first voltage measuring device (MU3) and a second voltage measuring device (MU4), as specified by the Fig. 1 shown, and also not via a first power measuring device (MP3) and a second power measuring device (MP4), as also shown by the Fig. Figure 1 shows that these are possible as optional variants, but would increase the size and cost of the circuit. For the same cost reasons, the circuit has only one current measuring device instead of two. The first current measuring device (MI3) and the second current measuring device (MI4) are shown in the Fig. 9 to a common total current measuring device (MI) 3_4 ) in the form of the lowest possible shunt resistor (R mb ) summarized. The voltage (U I_istb ), which are connected to the shunt resistance (R mb ) relative to the supply voltage (U bThe voltage drop is a measure of the total current (I3+I4) through the loads (11). This total current (I3+I4) is regulated by a total current regulating transistor (TR). s ), which is preferably a P-channel transistor. For this purpose, the sum current control transistor (TR ) is used. s ) with a target voltage (U Isoll ), typically supplied from a current mirror (not shown) and / or from external sources to the control circuit (10). This setpoint voltage (U) Isoll ) corresponds to the target value (I sum ) for the sum flows (I3+I4) in Fig. 1. The sum current control transistor (TR) s ) and the shunt resistance (R mb ) formed sum current source (IS 3_4 ) feeds a differential amplifier transistor pair (TR3 / TR4), consisting of the first control transistor (TR 3b ) and the second control transistor (TR 4b), which can also be parallel circuits of several transistors and / or more complex circuit blocks with similar functionality. The two control transistors (TR 3b , TR 4b ) are preferably P-channel transistors. The first control transistor (TR) 3b ) is connected with its drain to the first output (3) of the control circuit (10). The second control transistor (TR 4b ) is connected with its drain to the second output (4) of the control circuit (10). As in Fig. 1. The first output (3) of the control circuit (10) is directly connected to the consumer (11), while the second output (4) of the control circuit (10) is indirectly connected to the consumer (11), which here is an exemplary LED chain, via the said second external resistor (R4).

[0056] The differential stage (TR3 / TR4) consists of the first control transistor (TR 3b ) and the second control transistor (TR 4b) is now controlled with the help of a first control voltage (U) ctr3 ) and a first reference voltage (U ref ) is controlled. If the first reference voltage (U) is present ref ) lower than the first control voltage (U ctr3 ) so the second control transistor (TR) conducts 4b ) better than the first control transistor (TR) 3b ) and a portion of the total current (I3+I4) that passes through the total current regulating transistor (TR) s ) is provided, flows through the second control transistor (TR) 4b ) and thus the second external resistor (R4), across which the aforementioned excess operating voltage drops, and thus the excess electrical power is converted into a second resistance loss power (P). R4 ) is implemented. In return, the current is passed through the first control transistor (TR). 3b ) reduced by the corresponding part, since the sum of the output currents (I3+I4) is controlled by the sum current regulating transistor (TR) s ) and its control voltage (UIsoll ) is specified. In extreme cases, the second control transistor (TR) takes over. 4b ) the sum of the output currents (I3+I4). This is at the transition from the second operating voltage range (B) to the third operating voltage range (C) in Fig. 5 the case.

[0057] Is the first reference voltage (U) ref ) higher than the first control voltage (U ctr3 ) so the second control transistor (TR) conducts 4b ) worse than the first control transistor (TR) 3b ) and a smaller part of the total current (I3+I4) which passes through the total current regulating transistor (TR) s ) is provided, flows through the second control transistor (TR) 4b ) and thus the second external resistor (R4), across which the aforementioned excess operating voltage drops, and thus the excess electrical power is converted into a second resistance loss power (P). R4 ) is implemented. In return, the current (I3) is passed through the first control transistor (TR).3b ) increased by the corresponding part, since the sum of the output currents (I3+I4) is controlled by the sum current regulating transistor (TR) s ) and its control voltage (U Isoll ) is specified. In extreme cases, the first control transistor (TR) takes over. 3b ) the sum of the output currents (I3+I4) completely. This is at the transition from the first operating voltage range (A) to the second operating voltage range (B) in Fig. 5. In the first operating voltage range, either the first control transistor (TR) conducts. 3b ) and the second control transistor (TR 4b ) is high impedance or the operating voltage (U) b ) is so small that even the first control transistor (TR) 3b ) can no longer be controlled. The first control voltage (U ctr3 ) is provided in this example by a comparator (Cmp1) which measures the measurement voltage (U I_istb ) at the shunt resistance (R mb ) with a second reference voltage (U ref2) for example, by calculating the difference. The shunt resistance (R mb ) represents the total current measuring device (MI) 3_4 ) the Fig. 8. The sum current control transistor (TRs) represents the sum current source (IS). 3_4 ) the Fig. 8 represents the differential stage consisting of the first control transistor (TR). 3b ) and second control transistor (TR 4b ) represents the sum switch (TR3 / TR4) of the Fig. 8 dar.

[0058] Since the use of such circuits for controlling headlights in automobiles is of particular interest, the use of P-channel transistors in automobiles is especially advantageous because the LEDs (11) can be operated with respect to ground (2), specifically the metallic body as ground, which reduces the wiring complexity in the automobile. Of course, implementation in an N-channel circuit is also possible, but this requires a shunt resistor (R). mb) directly near the LEDs and / or requires an additional return wire.

[0059] The circuit of the Fig. However, version 9 has some disadvantages. Due to the stacking of a first transistor layer, consisting of the sum current control transistor (T), s ), and a second transistor level, consisting of the first control transistor (TR 3b ) and the second control transistor (TR 4b The transistors must have the same on-resistance R to function correctly. on To be able to carry the same total current (I3+I4, I3+I4+I8) as a single-stage solution, its size is doubled for this reason alone.

[0060] Fig. Figure 10 shows a simple schematic simplification of such a solution. Fig. 1 for a simplified implementation that avoids the disadvantages of the previous solution according to the Fig. 9 does not have. A total current measuring device (MI) 3_4) again measures the sum (I3+I4) of the output currents (I3, I4). This sum current measuring device thus replaces the first current measuring device (MI3) of the Fig. 1 and the second current measuring device (MI4) of the Fig. 1. It provides an actual value for the total current (I3+I4) to the controller (RG). Based on this, the controller (RG) then controls two independent regulated current sources (IS3, IS4) that draw a total current (I3+I4) from the supply line (1) and generate a first output current (I3) and a second output current (I4). The total current source (IS3+I4) 3_4 ) the Fig. Point 8, with its disadvantages, has been eliminated. The two output currents (I3, I4) are now controlled by the controller depending on a control signal (I). 3_4 ) regulated.

[0061] When operating correctly, the device will Fig. 10 also a method for the regulated supply of a consumer (11) with electrical energy by means of a control circuit (10) which includes the following steps: • Feeding a first output current (I3) into the first terminal (5) of the consumer (11) through a first controllable current source (IS3), which is connected on the other side with low resistance to a supply line (1). • Simultaneous injection of a second output current (I4) into the said first terminal (5) of the consumer (11) by means of a series connection of a second adjustable current source (IS4) and a second external electrical resistance (R4), which is connected on the other side with low resistance to the said supply line (1). • Control of the first output current (I3) and the second output current (I4) by a controller (RG) depending on a measurement parameter (I) 3_4 ) in such a way that with increasing operating voltage (U b ) • in a first operating voltage range (A) only the first controllable current source (IS3) delivers a non-zero output current (IS3) • and then in a second operating voltage range (B) immediately adjacent to the first operating voltage range (A), the second current source (IS4) provides a non-zero second output current (I4), which increases with increasing operating voltage (U) b ) increases, delivers, whereby the first output current (I3) of the first current source (IS3) is reduced by the value of this second output current (I4) and • and then in a third operating voltage range (C) immediately adjacent to the second operating voltage range (B), the second current source (IS4) supplies a voltage (U) b) provides an independent and non-zero second output current (I4) and the first output current (I3) of the first current source (IS3) is negligible, but at least less than 1% of the second output current (14).

[0062] Preferably, the sum current of the output currents (I3, I4, I8) of several current sources (IS3, IS4, IS8) is measured by a sum current measuring device (MI). 3_4 ), in particular a shunt resistance (R mb ). recorded. Their output signal (I 3_4 , U l_istb ) is then used as a measurement parameter for the independent control of the first output current (I3) and the second output current (I4) via a control signal (U) each. ctr3 , U ctr4 ) by a controller (RG) depending on this measurement parameter (I 3_4 , U l_istb ) used.

[0063] A corresponding concrete exemplary implementation of the Fig. 10 is in Fig. 11 shown. The sum current control transistor (TRs ) out of Fig. Number 9 has been omitted. The shunt resistance (R) mb The resistance should be so low that current-voltage feedback across this resistor can be neglected. A value of a few ohms for the shunt resistor (R) is suitable. mb ) is therefore recommended. Under this condition, the two control transistors (TR) can be used. 3b , TR 4b The current sources formed (IS3, IS4) are to be considered as separate current sources, as required, which are controlled independently of each other by means of two control voltages (U). ctr3 , U ctr4 ) are controlled. As previously in the Fig. 9 can now be connected to the shunt resistor (R mb ) a measuring voltage (U l_istb ) are measured, which are then measured again by a comparator (Cmp1) with a target voltage (U) l_soll ) is compared, which in its function corresponds to the target value (I sum ) for the current sum (I3+I4) from Fig. 1 corresponds to this. The comparator (Cmp1) generates the first control voltage (U) from this. ctr3 ) which directs the current (I3) through the first regulating transistor (TR) 3b ) is set. A differential voltage (U) is applied to this first control voltage. off ) added with the help of a voltage source, thereby creating the second control voltage (U) ctr4 ) is formed. With this second control voltage (U) ctr4 ) the second output current (I4) is controlled by the second regulating transistor (TR) 4b ) set. By appropriately choosing the sign and the voltage value of the differential voltage (U). off ) it is now ensured that the second transistor (TR 4b ) only begins to conduct from the boundary between the first operating voltage range (A) and the second operating voltage range (B), while the first control transistor (TR) 3b ) already begins conducting in the first operating voltage range (A) from the very beginning. This corresponds to the desired behavior from Fig. 5. The control transistors are preferably manufactured in matching units, but not necessarily with identical dimensions. This results in a power curve as shown in Fig. 6. Due to the elimination of the total current control transistor (T s ) is the required silicon area of ​​an integrated solution by roughly a factor of 2 compared to the solution from Fig. 9 reduced, which represents a significant commercial advantage. Furthermore, the solution is low-drop capable, meaning the controller performs significantly better with a smaller voltage drop from the operating voltage (U). b ) in the event of a voltage drop, as the solution from Fig. 9. Since the system is usually limited by the maximum power dissipation of the controller, a circuit of Fig. 9 compared to a circuit of Fig. 11 again by a factor of 2 due to the doubled power loss in the total current control using the total current control transistor (T s ) and limited in the difference stage (TR3 / TR4), resulting in an overall disadvantage of a factor of 4 in maximum power output.

[0064] Fig. 12 shows the solution from Fig. 11 with a more concrete design of the voltage source for the differential voltage (U off The comparator (Cmp1) supplies the control voltage (U). ctr ). A first amplifier (V3) generates a first offset voltage (U) from this by suitable amplification and addition. off3 ) the first control voltage (U ctr3 ), which, as in Fig. 11 is used as described. A second amplifier (V4) generates from the control voltage (U) ctr ) by suitable amplification and addition of a second offset voltage (U off4 ) the second control voltage (U ctr34 ), which, as in Fig. The method described in section 11 is used. Typically, the gains of the two amplifiers (V3, V4) are chosen to be one. It is particularly advantageous to set the first offset voltage (U) to 1. off3 ) to choose zero (0V), because then the first amplifier (V3) can be omitted and the first control voltage (U) ctr3 ) with the control voltage (U ctr ) out of Fig. 11 becomes identical. In that case, the second offset voltage (U) off4 ) with the differential voltage (U off ) out of Fig. 11 identical.

[0065] Fig. Figure 13 shows a generalization of the circuit diagram of the Fig. 12, where the two current sources (IS3, IS4) are also capable of supplying negative currents. This is particularly advantageous when, for example, inductive loads and motors are to be driven. In the broadest sense, it is an electronic half-bridge, which, as is common in power electronics, can be used in a variety of ways to control loads. With a circuit configuration as shown below... Fig. 15. This would result, for example, in an H-bridge, as is known from power electronics, albeit without the modification according to the invention. The major advantage of a half-bridge according to the invention is that, with the device according to the invention, direct sine wave control without harmonics is possible in EMC-sensitive areas at a higher output power. In contrast, PWM systems exhibit harmonics that, on the one hand, lead to undesirable emissions and, on the other hand, can cause undesirable noise in motors.

[0066] The device of Fig. 13 initially contains all elements of the device from Fig. 12. These are additionally identified in the index of the reference symbol by an extra "b". The first amplifier (V3) of the Fig. 12, there designated (V3), is therefore here, for example, designated (V 3b ). marked. Parallel to the two power sources from Fig. 12, consisting of the first amplifier (V 3b ), the second amplifier (V 4b ), the first control transistor (TR 3b ), the second control transistor (TR 4b ), the measuring resistor (R mb ), are two additional parallel current sources, consisting of the additional first amplifier (V 3c ), the additional second amplifier (V 4c ), the additional first control transistor (TR 3c ), the additional second control transistor (TR 4c ), the additional measuring resistor (R mc), switched. The additional measuring resistor (R mc However, it is not connected to the supply voltage line (1), but to the ground line (2) or a negative supply voltage line. The total current (I3+I4) is now calculated as the difference of the partial total currents by the subtractor (Delta1) from the two partial measurement voltages (U). I_istb , U I_istc ) and the operating voltage (U b ) as a control signal (U I_ist_b ) determined. The two partial measurement voltages (U l_istb , U l_istc ) are each obtained as a voltage measurement across the respective shunt resistor (R) mb , R mc The result is again a measured voltage (U). I_ist_b ), which now represents both currents. The additional regulating transistors (TR) 3c , TR 4c ) are preferably complementary to the first two control transistors (TR) 3b , TR 4b), so typically implemented as N-channel transistors, while the two control transistors (TR 3b , TR 4b ) preferably, as already described, implemented as P-channel transistors. Of course, a suitable circuit for the control transistors (TR) 3b , TR 4b , TR 3c , TR 4c A version using only N-channel or P-channel transistors is also conceivable. In particular, the version using only N-channel transistors offers a further area gain of almost a factor of 2. For this, only the offset voltages (U) need to be considered. off3b , U off4b , U off3c , U off4c ) the amplifier (V 3b , V 4b , V 3c , V 4c ) and the signs of the gains of the same are different than when using P-channel transistors for the control transistors (TR) 3b , TR 4b ) are chosen.

[0067] The offset voltages (Uoff3b , U off4b , U off3c , U off4c ) and sign of the amplifiers (V 3b , V 4b , V 3c , V 4c ) are preferably chosen in such a way that for the branch which the Fig. 12 corresponds to a behavior accordingly Fig. 5 and Fig. 6 results and analogously, only with negative current values, this also applies to the Fig. This results in 12 additional branches. Furthermore, no cross-currents may occur. Therefore, the regulating transistors (TR) must 3b , TR 4b ) be closed if one of the additional control transistors (TR) 3c , TR 4c ) leads.

[0068] Such a stage still roughly corresponds in its structure to the Fig. 9, whereby the power sources can now also supply negative current values.

[0069] In Fig. 14 This is now used to create two half-bridges, accordingly Fig. 13, an H-bridge to supply a consumer (Z L ). The H-bridge supplies the power via the aforementioned two half-bridges accordingly. Fig. 13 the complex load (Z L ) via two load connections (5, 6). More complex uses of half-bridges are known from the prior art, for example for the generation of multiphase signals at loads, such as in connection with three-phase motors and multiphase transformers, and are therefore not discussed further here. However, the use of half-bridges with properties according to the invention in such contexts is expressly part of this disclosure. The H-bridge therefore has two such connections (3b, 3d) instead of a single first connection (3) and two such connections (4b, 4d) instead of a single second connection (4).

[0070] The load (Z) is located there L ) between two half-bridges, corresponding to those in Fig. 13.

[0071] The first connection (5) of the load (Z) L ) is connected to a circuit accordingly Fig. 13 (also corresponds to Fig. 10) controlled via a first connection (3b) and a second connection (4b), while now the other, second connection (6) of the load is also connected to a circuit accordingly Fig. 13 (also corresponds to Fig. 10) is controlled via a third connection (4d) and a fourth connection (4e). Thus, the load (6) is now controlled by two half-bridges according to the Fig. 10 and Fig. 13 are controlled. For better differentiation, the components of the second half-bridge are in Fig. 14 with the differing indices “d” and “e” compared to the indices “b” and “c” of the Fig. 13. The total currents of the sub-branches of the first half-bridge are labeled here with I. 3bc and I 4bc denoted, while the sum currents of the second half-bridge are denoted by I 3de and I 4deare designated. The currents I 3de and I 3bc For each half-bridge, this corresponds to the output current I3 of the Fig. 1. The currents I 4de and I 4bc For each half-bridge, this corresponds to the output current I4 of the Fig. 1. The function of a component of the first half-bridge with index "b" always corresponds to the function of a component of the second half-bridge with index "d". The function of a component of the first half-bridge with index "c" always corresponds to the function of a component of the second half-bridge with index "e".

[0072] Fig. Figure 15 shows the generalization of such a full bridge according to the invention, consisting of two half bridges according to the invention, by generalizing the Fig. 1.

[0073] Using two half-bridges, accordingly Fig. 1. A full bridge, also called an H-bridge, is now constructed to supply a consumer (Z). The H-bridge supplies the consumer via the aforementioned two half-bridges accordingly. Fig. 1. The complex load Z is connected via two terminals (5, 6) of the load (Z). More complex uses of half-bridges are known from the prior art, for example, for generating multiphase signals at loads, particularly in connection with three-phase motors and multiphase transformers, and are therefore not discussed further here. Such applications would then require more than two half-bridges. The following are described Fig. 16, Fig. 21 and Fig. Figure 25 shows such exemplary applications with three consumer connections. The use of half-bridges with properties according to the invention in such contexts is therefore expressly part of this disclosure. In this regard, reference is made to the extensive literature on the use of half-bridges from the prior art.

[0074] This disclosure focuses on supplying the half-bridges according to the invention from a vehicle electrical system, which is typically a direct current (DC) system. However, use in AC power systems is also conceivable.

[0075] The H-bridge according to the invention therefore has, instead of a single first connection (3) in the example of the Fig. 15 via two such connections (3, 8). The additional connection (8) is described below. Fig. 15 and the claims are designated as the third connection. Furthermore, the H-bridge according to the invention has, instead of a single second connection (4) in the example of the Fig. 15 via two such connections (4, 9). This additional connection (9) is described below. Fig. 15 and the claims are designated as the fourth connection. The load (Z) is again located between the two half-bridges, according to the positioning in Fig. 14. The first terminal (5) of the load (Z) is connected to a circuit accordingly Fig. 1 is controlled, while now the other, second connection (6) of the load (Z) is also connected to a circuit accordingly Fig. 1 is controlled. Thus, the load (Z) is now controlled by two half-bridges according to the Fig. 1 is controlled. For better differentiation, the components of the second half-bridge are in Fig. 15 with the differing indices “8” and “9” compared to the indices “3” and “4” of the Fig. The sum currents of the first half-bridge are labeled I3+I4, while the sum currents of the second half-bridge are labeled I8+I9. The function of a component of the first half-bridge with index "3" always corresponds to the function of a component of the second half-bridge with index "9". The function of a component of the first half-bridge with index "4" always corresponds to the function of a component of the second half-bridge with index "8". It is obvious that the sum of the sum currents I3+I4+I8+I9 should always be zero to prevent charging of the load (Z). The controller should therefore calculate this sum internally, either analogously and / or digitally, to infer leakage currents and / or to balance the H-bridge. In this example, the control is thus performed by a common controller (RG). Since the principle of the control has already been explained, it will not be discussed further here, except for the regulation of the sum.

[0076] As already mentioned, consumers can have more than two supply connections.

[0077] Electric motors are one example. Fig. Figure 16 shows the control circuit for an example BLDC electric motor in a star connection. Of course, it can also be used with motors in a delta connection or with motors with an even higher number of coils. In the latter case, the number of half-bridges must be adjusted accordingly.

[0078] In principle, this represents a tripling of the number of power sources compared to the previous version. Fig. 10. There are three groups of power sources, each corresponding to a structure Fig. 10 and preferably Fig. 13 or Fig. 14 or variations thereof. To better distinguish the elements of the current source groups, these are compared. Fig. 9 with additionally added indices. The additions (“ _1 “, “ _2 “, “ _3 “) are appended to the original indices. The three star-connected loads (Z1, Z2, Z3) of the exemplary stator coil of the exemplary load of a BLDC motor are each connected with a separate thermal resistance (R). 4_1 , R 4_2 , R 4_3 ) operated.

[0079] Fig. Figure 17 shows another possibility for improving the output power parameters. If the power is not limited by the maximum temperature of the control system in the housing, but by the temperature at the upper operating voltage limit of the third operating voltage range (C), then it is advantageous to further increase the operating voltage (U) b ) the current through the second control transistor (TR 4b ) (see also Fig. 12) in an inserted fifth operating voltage range (E) so that the power output through this second control transistor (TR) 4b ) remains constant and therefore uses the first control transistor (TR) 3b ) to open to such an extent that its maximum output power is delivered in the form of a non-zero first output current (I3). This causes the first control transistor (TR) to take over. 3b ) in this case again a portion of the load, which further reduces the chip area in the case of an integrated controller.

[0080] Fig. 18 shows the Fig. 17 suitable power ratios. In the additional fifth operating voltage range (E), the power at the external second winding resistor (R4) remains constant and does not increase. The LED power dissipation (P LEDThe voltage also remains constant. The third current source (IS3) then takes over some of the additional power that must be supplied by the two current sources, delivering a small current. However, due to the high voltage, this leads to a significant heating of the first current source (IS3). Therefore, the maximum current of the first current source (IS3) in the fifth operating voltage range (€) is considerably reduced compared to the maximum current of the first current source (IS3) in the second operating voltage range (B). Such current transfer by the first current source is only advantageous if the power of the second current source (IS4) is limited not by the maximum system temperature, but by the temperature of the associated second control transistor (TR). 4b ) is limited.

[0081] The Fig. 19 to 21 show the Fig. 1, Fig. 3 and Fig. 4 with inductive load (Z, Z1, Z2, Z3) and the corresponding freewheeling diodes. The advantage of the device according to the invention is the ability to generate sinusoidal control signals with low EMC emissions.

[0082] The Fig. 22 to 25 show the Fig. 1 to 4 with capacitive load (16, 16_1, 16_2, 16_3)

[0083] Fig. Figure 26 shows a simple exemplary implementation of a device according to the Fig. 9.

[0084] The Fig. However, device 9 did not have these measuring devices. It also did not have a first power measuring device (MP3) and a second power measuring device (MP4), as also stated by the Fig. 1 shown. The first current measuring device (MI3) and the second current measuring device (MI4) of the Fig. 1 are included in the implementation proposal of the Fig. 26 was also not included.

[0085] The exemplary device of the Fig. However, MU1 had a first voltage measuring device (MU3) and a second voltage measuring device (MU4). In the exemplary implementation of the Fig. Figure 26 is an exemplary implementation of the first voltage measuring device (MU3) in the form of a voltage divider consisting of a first measuring resistor (R) mb1 ) and a second measuring resistor (R mb2 ) provided, which provides a voltage actual signal (U v_istb ) is generated, which is fed back to the comparator (Cmp1) as before and there regulates the total current (I3+I4) and the distribution of the total current (I3+I4) to the first output current (I3) and the second output current (I4).

[0086] The combination with the other control variables mentioned in the description, features, and requirements is of course also possible in a circuit. The rest is described below. Fig. 9, Fig. 11, Fig. 12, Fig. 13, Fig. The provision described in section 14 is applicable here by analogy and is therefore part of this disclosure.

[0087] The Fig. 26 is therefore an example of regulating the total current using the load voltage.

[0088] The voltage (U V_istb ), which are connected to the voltage divider (R mb1 , R mb2 The voltage drop relative to ground is a measure of the load voltage across the load (11). The summation current control transistor (TR s ) out of Fig. Figure 9 has been omitted here, but would of course be conceivable, even without a corresponding drawing included. The measuring resistors (R mb1 , R mb2 The resistors are chosen to have such high resistance that the measuring current through the voltage divider is, if possible, less than 10%, preferably less than 5%, preferably less than 1% of the sum of the currents (I3+I4) of the first output current (I3) and the second output current (I4), in order to avoid unnecessarily loading the driver. The two control transistors (TR) 3b , TR 4bThe current sources formed (IS3, IS4) can be considered separate current sources here due to their direct coupling to the supply line, which can be controlled independently of each other using two control voltages (U). ctr3 , U ctr4 ) are controlled. The voltage divider (R) mb1 , R mb2 ) measured measuring voltage (U V_istb ) is again passed through a comparator (Cmp1) with a target voltage (U) I_soll ) compared, which in their function again corresponds to the setpoint (I sum ) for the current sum (I3+I4) from Fig. 1 corresponds. The comparator (Cmp1) generates from this again, as in Fig. 11, the first control voltage (U ctr3 ) which directs the current (I3) through the first regulating transistor (TR) 3b ) is set. A differential voltage (U) is applied to this first control voltage. off ) added with the help of a voltage source, thereby creating the second control voltage (U) ctr4 ) is formed. With this second control voltage (U) ctr4) the second output current (I4) is controlled by the second regulating transistor (TR) 4b ) set. By appropriately choosing the sign and the voltage value of the differential voltage (U). off ) will now be used again, as in Fig. 11, ensured that the second transistor (TR 4b ) only begins to conduct from the boundary between the first operating voltage range (A) and the second operating voltage range (B), while the first control transistor (TR) 3b ) already begins conducting in the first operating voltage range (A) from the very beginning. This again corresponds to the desired behavior from Fig. 5 is applied here only to a voltage source. The control transistors are preferably manufactured in matching pairs, but not necessarily with identical dimensions. This again results in a power curve as in Fig. 6. Furthermore, this solution is also low-drop capable, meaning that the controller performs significantly better with a smaller voltage drop below the operating voltage (U). b ) in the event of a voltage dip, than a solution with a summation current source transistor (TR) s ), which is not shown here. Since the system is usually limited by the maximum power dissipation of the controller, a circuit with such a summation current source transistor (TR) s ) compared to a circuit of Fig. 26 again by a factor of 2 due to the doubled power loss in the total current control using the total current control transistor (T s ) and limited in the difference stage (TR3 / TR4), so that here too there is an overall disadvantage of factor 4 in the maximum power output.

[0089] Fig. 27 shows a mixture of the systems from Fig. 26 and Fig. 11 as an example of a mixed system, where the measuring resistor (R m ) for the total current is inserted elsewhere, namely between ground and the second load connection (6). This resistance can be external or internal. In the latter case, the system requires an additional connection (17), which increases the cost of the system's housing. By multiplying the measured current (U) I_istb ) with the voltage measurement (U V_istb ) for example in an analog multiplier (MUL) an actual value (U) results P_istb ) for the consumer power (P3+P4), which is a summation of the first power measuring device (MP3) and the second power measuring device (MP4) into a total power measuring device (MP 3_4 ) corresponds.

[0090] The voltage (U P_istb The current-voltage (TR) obtained in this way in this example is a measure of the controller's output power to the load (11). The sum current control transistor (TR) s) out of Fig. Number 9 has also been omitted here, but would of course be conceivable, even without a corresponding drawing included. The measuring resistors (R mb1 , R mb2 The resistors are again chosen to have such a high resistance that the measuring current through the voltage divider is, if possible, less than 10%, preferably less than 5%, preferably less than 1% of the sum of the currents (I3+I4) from the first output current (I3) and the second output current (I4), in order to avoid unnecessarily loading the driver. The measuring resistor (R mb ) should also be chosen to be sufficiently low. The two control transistors (TR 3b , TR 4b The current sources formed (IS3, IS4) can again be considered separate current sources due to their direct coupling to the supply line, which can be controlled independently of each other using two control voltages (U). ctr3 , U ctr4 ) are controlled. That's part of the Fig. 11, Fig. 12, Fig. 13 and Fig. Point 14 also applies here. The power measurement voltage (U) P_istb ) is again passed through a comparator (Cmp1) with a target voltage (U) I_soll ) compared, which in their function now here corresponds to the target value (I sum ) for the power sum (P3+P4). The comparator (Cmp1) generates from this again, as in Fig. 11, the first control voltage (U ctr3 ) which directs the current (I3) through the first regulating transistor (TR) 3b ) is set. A differential voltage (U) is applied to this first control voltage. off ) added with the help of a voltage source, thereby again the second control voltage (U) ctr4 ) is formed. With this second control voltage (U) ctr4 ) the second output current (I4) is controlled by the second regulating transistor (TR) 4b ) set. By appropriately choosing the sign and the voltage value of the differential voltage (U). off ) will now be used again, as in Fig. 11, ensured that the second transistor (TR 4b) only begins to conduct from the boundary between the first operating voltage range (A) and the second operating voltage range (B), while the first control transistor (TR) 3b ) already begins conducting in the first operating voltage range (A) from the very beginning. This again corresponds to the desired behavior from Fig. 5 is applied here only to a voltage source. The control transistors are preferably manufactured in matching pairs, but not necessarily with identical dimensions. This again results in a power curve as in Fig. 6. Furthermore, this solution is also low-drop capable, meaning that the controller performs significantly better with a smaller voltage drop below the operating voltage (U). b ) in the event of a voltage dip, than a solution with a summation current source transistor (TR) s), which is not shown here. Since the system is usually limited by the maximum power dissipation of the controller, a circuit with such a summation current source transistor (TR) s ) compared to a circuit of Fig. 27 again by a factor of 2 due to the doubled power loss in the total current control using the total current control transistor (T s ) and limited in the difference stage (TR3 / TR4), so that here too there is an overall disadvantage of factor 4 in the maximum power output. Reference symbol list 1 Supply voltage connection of the control circuit according to the invention (10) 2 Ground connection of the control circuit according to the invention (10) (reference potential) 3 First output of the control circuit (10) 3_1 First output of the control circuit (10_1) for red 3_2 First output of the control circuit (10_2) for green 3_3 First output of the control circuit (10_3) for blue 3 b First output of the control circuit in the first half-bridge of the Fig. 14 3 d First output of the control circuit in the second half-bridge of the Fig. 14 4 Second output of the control circuit (10) 4_1 Second output of the control circuit (10_1) for red 4_2 Second output of the control circuit (10_2) for green 4_3 Second output of the control circuit (10_3) for blue 4 b Second output of the control circuit (10) in the first half-bridge of the Fig. 14 4 d Second output of the control circuit (10) in the second half-bridge of the Fig. 14 5 First connection of the consumer (11, Z L ) 5_1 First connection of the red LED chain (11_1) 5_2 First connection of the green LED chain (11_2) 5_3 First connection of the blue LED chain (11_3) 6 Second connection of the consumer (11, Z L ) 6_1 Second connection of the red LED chain (11_1) 6_2 Second connection of the green LED chain (11_2) 6_3 Second connection of the blue LED chain (11_3) 7 Energy source 8 Third output of the control circuit (10) 9 Fourth output of the control circuit (10) 10 Control circuit 10_1 Control circuit of the red LED chain (11_1) 10_2 Control circuit of the green LED chain (11_2) 10_3 Control circuit of the blue LED chain (11_3) 11. Consumers. The consumer can also be a network of consumers. In particular, it can be an LED or a series or parallel connection of LEDs. It can also be, for example, a complex load (Z). L ), an inductor or a resistive load or an electric machine or a loudspeaker or a capacitive load or a motor. 11_1 Red LED chain as a consumer (11) 11_2 Green LED chain as a consumer (11) 11_3 Blue LED chain as a consumer (11) 12 Second control circuit 13 Second consumer 14 First freewheeling diode 14_1 First freewheeling diode of the first half-bridge of the Fig. 21 14_2 First freewheeling diode of the second half-bridge of the Fig. 21 14_3 First freewheeling diode of the third half-bridge of the Fig. 21 15 Second freewheeling diode 15_1 Second freewheeling diode of the first half-bridge of the Fig. 21 15_2 Second freewheeling diode of the second half-bridge of the Fig. 21 15_3 Second freewheeling diode of the third half-bridge of the Fig. 21 16 Capacitive Load 16_1 Capacitive load of the first half-bridge in Fig. 25 16_2 Capacitive load of the second half-bridge in Fig. 25 16_3 Capacitive load of the third half-bridge in Fig. 25 A First operating voltage range ADC Analog-to-Digital Converter B Second operating voltage range C Third operating voltage range C1 First half of the third operating voltage range, in which the power across one of the external resistors (R4, R8) is constant. C2 Second half of the third operating voltage range, in which the power across both external resistors (R4, R8) is constant. Cmp1 First Comparator Cmp 1b First comparator in the first half-bridge of the Fig. 14 Cmp 1d First comparator in the second half-bridge of the Fig. 14 CTR Controller for controlling the control circuit (10) D Fourth operating voltage range Delta, differential generator for generating the measuring voltage (U) I_ist_b) for controlling the comparator (Cmp1) in the half-bridge of the Fig. 13. The addition of the operating voltage (U b ) is in Fig. 13 not shown. delta 1b Differential generator for generating the measuring voltage (U) I_ist_b ) for controlling the comparator (Cmp 1b ) in the first half-bridge of the Fig. 14. The addition of the operating voltage (U b ) is in Fig. 14 not shown. delta 1d Differential generator for generating the measuring voltage (U) I_ist_d ) for controlling the comparator (Cmp 1d ) in the second half-bridge of the Fig. 14. The addition of the operating voltage (U b ) is in Fig. 14 not shown. E Fifth operating voltage range FD Fault Detection. The fault detection system receives measured values ​​from the various measuring instruments and the fault signals S. stat_extthe external signaling device. From this, the fault detection system determines the system's state. If a fault is present, it is detected and the system is brought to a safer operating state. The fault detection system typically overrides other controllers and specifications. The fault detection system signals a faulty state externally via the fault signal (S). stat ). FR Color Control The color control receives at least one measured value from at least one color sensor (MF) and generates setpoint values ​​for the various control circuits (10_1, 10_2, 10_3) from it. I3 Output current of the first output (3) of the control circuit (10) I 3_1 Output current of the first output (3_1) of the first half-bridge of the control circuit (10) in Fig. 16. This can be done using negative and positive values ​​of the output current I. 3_1 It can be assumed that there is a half-bridge according to Fig. 13 would be an exemplary realization of the associated power source IS 3_1 . I 3_2 Output current of the first output (3_2) of the second half-bridge of the control circuit (10) in Fig. 16. This can be done using negative and positive values ​​of the output current I. 3_2 It can be assumed that there is a half-bridge according to Fig. 13 would be an exemplary realization of the associated power source IS 3_2 . I 3_3 Output current of the first output (3_3) of the third half-bridge of the control circuit (10) in Fig. 16. This can be done using negative and positive values ​​of the output current I. 3_3 It can be assumed that there is a half-bridge according to Fig. 13 would be an exemplary realization of the associated power source IS 3_3 . I 3_4 Measured value of the sum of the output currents (I3+I4) I 3bOutput current of the first output (3, 3b) of the control circuit (10) for positive currents in the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13 I 3bc Subtotal flow of individual flows I 3b and I 3c the first half-bridge in Fig. 14 and the half-bridge in Fig. 13. In the case of the Fig. 14 around the output current at the first terminal (3 b ) of the first half-bridge. I 3c Output current of the first output (3, 3b) of the control circuit (10) for negative currents in the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13 I 3d Output current of the first output (3d) of the control circuit (10) for positive currents in the second half-bridge of the Fig. 14 I 3de Subtotal flow of individual flows I 3d and I 3e the second half-bridge in Fig. 14. This is the case with the Fig. 14 around the output current at the fourth terminal (3d) of the first half-bridge. I 3d Output current of the first output (3d) of the control circuit (10) for negative currents in the second half-bridge of the Fig. 14 I4 Output current of the second output (4) of the control circuit (10) I 4_1 Output current of the second output (4_1) of the first half-bridge of the control circuit (10) in Fig. 16. This can be done using negative and positive values ​​of the output current I. 4_1 It can be assumed that there is a half-bridge according to Fig. 13 would be an exemplary realization of the associated power source IS 4_1 . I 4_2 Output current of the second output (4_2) of the second half-bridge of the control circuit (10) in Fig. 16. This can be done using negative and positive values ​​of the output current I. 4_2 It can be assumed that there is a half-bridge according to Fig. 13 would be an exemplary realization of the associated power source IS 4_2 . I 4_3 Output current of the second output (4_3) of the third half-bridge of the control circuit (10) in Fig. 16. This can be done using negative and positive values ​​of the output current I. 4_3 It can be assumed that there is a half-bridge according to Fig. 13 would be an exemplary realization of the associated power source IS 4_3 . I 4b Output current of the second output (4, 4b) of the control circuit (10) for positive currents in the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13 I 4bc Subtotal flow of individual flows I 4b and I 4c the first half-bridge in Fig. 14 and the half-bridge in Fig. 13. In the case of the Fig. 14 around the output current at the second terminal (4 b ) of the first half-bridge. I 4cOutput current of the second output (4, 4b) of the control circuit (10) for negative currents in the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13 I 4d Output current of the second output (4d) of the control circuit (10) for positive currents in the second half-bridge of the Fig. 14 I 4de Subtotal flow of individual flows I 4d and I 4e the second half-bridge in Fig. 14. This is the case with the Fig. 14 around the output current at the third terminal (4d) of the first half-bridge. I 4e Output current of the second output (4d) of the control circuit (10) for negative currents in the second half-bridge of the Fig. 14 I8 Output current of the third output (8) of the control circuit (10) I9 Output current of the fourth output (9) of the control circuit (10) (I3+I4) Sum of the output currents, namely the output current I4 of the second output (4) and the output current I3 of the first output (3) (I 3b +I 4b Sum of the output currents, specifically the output current I4 +I 3c +I 4c ) = of the second output (4, 4b) and of the output current I3 of the (I 3bc +I 4bc ) first exit (3, 3b) in the first half-bridge of figure I4 and in the half-bridge of the Fig. 13 (I 3d +I 4d Sum of the output currents, specifically the output current I4 +I 3e + I 4e ) = of the second output (4d) and of the output current I3 of the (I 3de +I 4de ) first exit (3d) in the second half-bridge of the Fig. 14 (I3+I4+I8) Sum of the output currents, namely the output current (I8) of the third output (8), the output current (I4) of the second output (4), and the output current (I3) of the first output (3) in Fig. 3. This current sum is used with three current sources (IS3, IS4, IS8). For more current sources, this sum is increased accordingly. intRef Internal References I ref_int Internal reference current for specifying the current sum (I3+I4, I3+I4+I8). IS3 First regulated current source that supplies the output current I3 of the first output (3). IS 3_1 First regulated current source that provides the output current I 3_1 of the first output (3_1) for the first half-bridge in Fig. 16 delivers. Here it is assumed that the regulated current source provides positive and negative output currents (I 3_1 can deliver. IS 3_2First regulated current source that supplies the output current I3_2 of the first output (3_2) for the second half-bridge in Fig. 16 delivers. Here it is assumed that the regulated current source provides positive and negative output currents (I 3_2 can deliver. IS 3_3 First regulated current source that provides the output current I 3_3 of the first exit (3_3) for the third half-bridge in Fig. 16 delivers. Here it is assumed that the regulated current source provides positive and negative output currents (I 3_3 can deliver. IS 3_4 Regulated total current source that supplies the total current (I3+I4). IS4 Second regulated current source that supplies the output current I4 of the second output (4). IS 4_1 Second regulated current source, which supplies the output current I 4_1 of the second output (4_1) for the first half-bridge in Fig. 16 delivers. Here it is assumed that the regulated current source provides positive and negative output currents (I 4_1 can deliver. IS 4_2 Second regulated current source, which supplies the output current I 4_2 of the second output (4_2) for the second half-bridge in Fig. 16 delivers. Here it is assumed that the regulated current source provides positive and negative output currents (I 4_2 can deliver. IS 4_3 Second regulated current source, which supplies the output current I 4_3 of the second exit (4_3) for the third half-bridge in Fig. 16 delivers. Here it is assumed that the regulated current source provides positive and negative output currents (I 4_3 can deliver. IS8 Third regulated current source that supplies the output current I8 of the third output (8). IS9 Fourth regulated current source that supplies the output current I9 of the fourth output (9). I sumTarget value for the current sum (I3+I4, I3+I4+I8, ,I3+I4+I8+I9). I rer_ext External reference current LED light-emitting diode MF color sensor MI3 First current measuring device for measuring the current I3 MI 3_4 Total current measuring device for measuring the sum of the output currents (I3+I4) ml 3_4_1 Total current measuring device for measuring the sum of the output currents (I 3_1 +I 4_1 ) the first half-bridge in Fig. 16 MI 3_4_2 Total current measuring device for measuring the sum of the output currents (I 3_2 +I 4_2 ) the second half-bridge in Fig. 16 MI 3_4_3 Total current measuring device for measuring the sum of the output currents (I 3_3 +I 4_3 ) the third half-bridge in Fig. 16 MI4 Second current measuring device for measuring the current I4 MI8 Third current measuring device for measuring the current I8 MU3 First voltage measuring device for measuring the voltage between the first output (3) of the control circuit (10) and the ground connection (2) of the control circuit (10) MU4 Second voltage measuring device for measuring the voltage between the second output (4) of the control circuit (10) and the ground terminal (2) of the control circuit (10) MU8 Third voltage measuring device for measuring the voltage between the third output (8) of the control circuit (10) and the ground terminal (2) of the control circuit (10) MU9 Fourth voltage measuring device for measuring the voltage between the fourth output (9) of the control circuit (10) and the ground terminal (2) of the control circuit (10) MP3 First power measuring device for measuring the power delivered at the gate consisting between the first output (3) of the control circuit (10) and the ground connection (2) of the control circuit (10) MP4 Second power measuring device for measuring the power delivered at the gate, consisting between the second output (4) of the control circuit (10) and the ground connection (2) of the control circuit (10) MP8 Third power measuring device for measuring the power delivered at the gate, consisting between the third output (8) of the control circuit (10) and the ground connection (2) of the control circuit (10) MP9 Fourth power measuring device for measuring the power delivered at the gate, consisting between the fourth output (9) of the control circuit (10) and the ground connection (2) of the control circuit (10) MT temperature measuring device, which measures the temperature, for example, in the control circuit (10) itself and / or in parts of the control circuit (10) and / or in the vicinity of the control circuit (10) and / or in the vicinity of at least one consumer (11) and / or in the vicinity of an external resistor (R3, R4, R8) and / or in the vicinity of a control transistor (TR3, TR4, TR s ) and / or measures near a power source (IS3, IS4, IS8). MU b Operating voltage measuring device for measuring the operating voltage U b P3 Power delivered by the control circuit (10) via the first output (3). P4 Power delivered by the control circuit (10) via the second output (4). P8 Power delivered by the control circuit (10) via the third output (8). P9 Power delivered by the control circuit (10) via the fourth output (9). P3+P4 Sum of the output powers of the first output (P3) and the second output (P4) P3+P4+P8 Sum of the output powers of the first output (P3), the second output (P4), and the third output (P3) P3+P4+P8+P9 Sum of the output powers of the first output (P3) and the second output (P4) and the third output (P8) and the fourth output (P9) P 10 Power loss in the control circuit (10) P LED LED power loss of the LEDs (of the consumer (11)), consumer power loss P R4 First resistance loss of the second external resistor R4 P R4 Second resistance loss of the second external resistor R4 P R8 Third resistance loss of the third external resistor R8 PWM Pulse Width Modulation R3 First external resistor R4 Second external resistor R4_1 Second external resistor of the red LED chain (11_1) R 4_2 Second external resistor of the green LED chain (11_2) R 4_3 Second external resistor of the blue LED chain (11_3) R8 Third External Resistor RefG Reference generation from external reference streams I ref_ext_1 ; I ref_ext_2 , I ref_ext_3 The currents are conducted across the resistors R ref_1 , R ref_2 , R ref_3 , set. The currents can be used for the basic setting of the sub-devices (10_1, 10_2, 10_3) using block RefG. RG regulator R mb Shunt resistor or measuring resistor for the positive current branch of the first half-bridge in Fig. 14 or the half-bridge in Fig. 13 or the power sources in Fig. 9, Fig. 11, Fig. 12. The shunt resistor is designed with the lowest possible resistance, as it increases the system's power dissipation and, if its resistance is too high, can cause undesirable feedback effects. It is used to measure the voltage U. I_istb at the shunt resistance R mb generated, which provides a measure of the positive sum current (I3+I4) through the measuring resistor R mb is. In that respect, this measuring resistor (R) represents mb ) the first current measuring device (MI3) for measuring the first output current (I3) and the second current measuring device (MI4) for measuring the second output current (I4) together. R mc Shunt resistor or measuring resistor for the negative current branch of the first half-bridge in Fig. 14 or the half-bridge in Fig. 13. The shunt resistor is designed with the lowest possible resistance, as it increases the system's power dissipation and, if its resistance is too high, can cause undesirable feedback effects. It is used to measure the voltage U. I_istc at the shunt resistance R mc generated, which provides a measure of the negative total current (I 3c +I 4c ) through the measuring resistor R mc is. R md Shunt resistor or measuring resistor for the negative current branch of the second half-bridge in Fig. 14. The shunt resistor is designed with the lowest possible resistance, as it increases the system's power dissipation and, if its resistance is too high, can cause undesirable feedback effects. It is used to measure the voltage U. I_istd at shunt resistance R md generated, which provides a measure of the total flow (I 3d +I 4d ) through the measuring resistor R md is. R meShunt resistor or measuring resistor for the negative current branch of the second half-bridge in Fig. 14. The shunt resistor is designed with the lowest possible resistance, as it increases the system's power dissipation and, if its resistance is too high, can cause undesirable feedback effects. It is used to measure the voltage U. I_istb at shunt resistance R me generated, which provides a measure of the negative total current (I 3e +I 4e ) through the measuring resistor R me is. R ref Reference resistor S stat Error signal S stat_ext External fault signal (an input signal of the control circuit (10)) ST data interface SUP supply of the control circuit (10) from the operating voltage supply (U b ) T Temperature. This is a symbol for one or more of the following temperatures: • the temperature (T) of the control circuit (10) • the temperature of a part of the control circuit (10) • the temperature near the control circuit (10) • the temperature near a load (11) • the temperature near a resistor (R3, R4) • the temperature near a control transistor (TR3, TR4, TR s ) • the temperature near a power source (IS3, IS4, IS8) T R Temperature of an external resistor (R3, R4, R 4_3 , R 4_2 , R 4_1 , R8) TR s Total current control transistor for regulating the total current (I3+I4) TR 3b First control transistor for regulating the current component of the first output (3) of the control circuit (10) in a configuration as two separately controlled current sources, wherein this first control transistor operates at lower operating voltages (Ub ) is opened as the second control transistor (TR) 4b ) according to Fig. 9, Fig. 11 or Fig. 12. The transistor is also found in the Fig. 13 and Fig. 14. TR 4b Second control transistor for regulating the current component of the second output (4) of the control circuit (10) in a configuration as two separately controlled current sources, wherein this second control transistor operates at higher operating voltages (U b ) is only opened when the first control transistor (TR) 3b ) according to Fig. 9, Fig. 11 or Fig. 12. The transistor is also found in the Fig. 13 and Fig. 14. U3 First output voltage, voltage between first output (3) and ground connection (2) U4 Second output voltage, voltage between second output (4) and ground connection (2) U3 Third output voltage, voltage between third output (8) and ground connection (2) U b Operating voltage. This is the voltage between the supply voltage terminal (1) of the control circuit (10) and the ground terminal (2) of the control circuit. The operating voltage is provided by the power supply (7). U ctr Control voltage for controlling the control transistors (TR) 3a , TR 4a , TR 3b , TR 4b ) U ctrb Control voltage for controlling the control transistors (TR) 3b , TR 4b , TR 3c , TR 4c ) in the first half-bridge of the Fig. 14 U ctrd Control voltage for controlling the control transistors (TR) 3d , TR 4d , TR 3e , TR 4e ) in the second half-bridge of the Fig. 14 U ctr3 First control voltage for controlling the first control transistors (TR) 3a , TR 3b ) U ctr3bFirst control voltage for controlling the first control transistors (TR) 3b , TR 3b ) in the first half-bridge of the Fig. 14 U ctr3c First control voltage for controlling the first control transistors (TR) 3c , TR 3c ) in the first half-bridge of the Fig. 14 U ctr3d First control voltage for controlling the first control transistors (TR) 3d , TR 3d ) in the second half-bridge of the Fig. 14 U ctr3e First control voltage for controlling the first control transistors (TR) 3e , TR 3e ) in the second half-bridge of the Fig. 14 U ctr4 Second control voltage for controlling the second control transistors (TR) 4a , TR 4b ) U ctr4b Second control voltage for controlling the second control transistors (TR) 4b , TR 4b ) in the first half-bridge of the Fig. 14 U ctr4cSecond control voltage for controlling the second control transistors (TR) 4c , TR 4c ) in the first half-bridge of the Fig. 14 U ctr4d Second control voltage for controlling the second control transistors (TR) 4d , TR 4d ) in the second half-bridge of the Fig. 14 U ctr4d Second control voltage for controlling the second control transistors (TR) 4e , TR 4e ) in the second half-bridge of the Fig. 14 U I_ist Measuring voltage across the shunt resistor (R mb This controls the input of the comparator (Cmp1), which supplies the control voltage (U) ctr ) or the first control voltage (U ctr3 ) generated. U I_istb Measuring voltage across the shunt resistor (R mb ) of the positive branch of the first semi-bridge of the Fig. 14 or the half-bridge of the Fig. 13 or the measuring voltage across the shunt resistor (R mb ) the Fig. 9, Fig. 11, Fig. 12 U I_ist_b Difference of the measured voltages U I_Istb and U I_istc at the two shunt resistors (R mb , R mc ) the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13. This controls the input of the comparator (Cmp). 1b ), which controls the voltage (U ctrb ) or generates the first control voltage (U) ctr3b , Uctr3c). U I_istc Measuring voltage across the shunt resistor (R mc ) negative branch of the first semi-bridge of the Fig. 14 and the half-bridge in Fig. 13 U I_istd Measuring voltage across the shunt resistor (R md ) the first semi-bridge of the positive branch Fig. 14 U I_ist_d Difference of the measured voltages U I_Iste and U I_istd at the two shunt resistors (R md , R me ) the second half-bridge of the Fig. 14. This controls the input of the comparator (Cmp).1d ), which controls the voltage (U ctrd ) or generates the first control voltage (U) ctr3d , U ctr3e ). U I_istb Measuring voltage across the shunt resistor (R me ) of the negative branch of the first semi-bridge of the Fig. 14 U Isoll Target voltage for the total current (I3+I4). This value corresponds in function to the target value (I sum ) for the total current (I3+I4, I3+I4+I8) in Fig. 1. U off Differential voltage for offset generation between the first control voltage (U ctr3 ) and second control voltage (U ctr4 ) This voltage (U off ) ensures in the case of the interconnections of the Fig. 11 and Fig. 12 for the second control transistor (TR) 4b ) later than the first control transistor (TR) 3b ) opens. U off3 First offset voltage between the control voltage (U ctr ) and first control voltage (U ctr3), which is converted by the first amplifier (V3) to the control voltage (U ctr ) is added. The sign and magnitude of this first offset voltage (U) off3 ) are chosen such that this first offset voltage (U off3 ) in conjunction with the second offset voltage (U off4 ) in the case of the interconnection of the Fig. 11 and Fig. 12 ensures that the second control transistor (TR) 4b ) later than the first control transistor (TR) 3b ) opens. Typically, the first offset voltage (U) off3 ) selected to zero (0V), thus setting the control voltage (U) ctr ) and the first control voltage (U ctr3 ) no longer differ and the first amplifier (V3) can be omitted. U off4 Second offset voltage between the control voltage (U) ctr ) and second control voltage (U ctr4 ,) which is converted to the control voltage (U) by the second amplifier (V4). ctr) is added. The sign and magnitude of this second offset voltage (U) off4 ) are chosen such that this second offset voltage (U off4 ) in conjunction with the first offset voltage (U off3 ) in the case of the interconnection of the Fig. 11 and Fig. 12 ensures that the second control transistor TR 4b later than the first control transistor (TR) 3b ) opens. Is the first offset voltage (U) off3 ) selected to zero (0V), thus setting the control voltage (U) ctr ) and the first control voltage (U ctr3 ) no longer differ, so this second offset voltage (U) is correct off4 ) with the differential voltage for offset generation (U off ) agree. In that case, the second amplifier (V4) corresponds to the Fig. 12 of the offset voltage source (U off ) the Fig. 11. U ref First reference voltage. The first reference voltage (U) ref) is chosen so that in the event of an excessively low operating voltage (U) b ) the first control transistor (TR 3a ) in Fig. 9 is open and at a sufficiently high operating voltage (U b ) the second control transistor (TR 4a ) takes over the current and thereby the first control transistor (TR) 3a ) in Fig. 9 is switched off, which changes the performance scheme of Fig. This results in 6. The total current (I3+I4) is controlled by the total current regulating transistor (TR). s ) depending on the target voltage (U Isoll ) set. U ref2 Second reference voltage. The second reference voltage establishes Fig. 9 determines the distribution of the total current (I3+I4) between the output current (I3) of the first output (3) of the control circuit (10) and the output current (I4) of the second output (4) of the control circuit (10). V3 First Amplifier V 3bFirst amplifier for the supply branch for positive output currents (I3, I) 3b +I 3c ) at the first exit (3, 3b) in the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13 V 3c First amplifier for the supply branch for negative output currents (I3, I 3b +I 3c ) at the first exit (3, 3b) in the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13 V 3d First amplifier for the supply branch for positive output currents (I 3d +I 3e ) at the first exit (3d) in the second half-bridge of the Fig. 14 V 3e First amplifier for the supply branch for negative output currents (I 3d +I 3e ) at the first exit (3d) in the second half-bridge of the Fig. 14 V4 Second Amplifier V 4b Second amplifier for the supply branch for positive output currents (I4, I4b +I 4e ) at the second exit (4, 4b) in the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13 V 4c Second amplifier for the supply branch for negative output currents (I3, I) 3b +I 3c ) at the second exit (4, 4b) in the first half-bridge of the Fig. 14 and in the half-bridge of the Fig. 13 V 4d Second amplifier for the supply branch for positive output currents (I 3d +I 3e ) at the second exit (4d) in the second half-bridge of the Fig. 14 V 4e Second amplifier for the supply branch for negative output currents (I 3d +I 3e ) at the second exit (4d) in the second half-bridge of the Fig. 14 V p Distribution parameters Z Complex load, especially inductive load Z L Complex load, especially inductive load Z1 Complex load, especially inductive load Z2 Complex load, especially inductive load Z3 Complex load, especially inductive load

Claims

[1] Method for the regulated supply of a consumer (11) with electrical energy by means of a control circuit (10) comprising the steps • Feeding a first output current (I3) into a first terminal (5) of the load (11) by means of a first controllable current source (IS3), which is part of the control circuit (10) and is connected on the other side with its second terminal at low resistance to a supply line (1, 2), via a first terminal of this current source (IS3) and • simultaneous injection of a second output current (I4) by a second adjustable current source (IS4), which is part of the control circuit (10), into a second output (4) of the control circuit (10) and from there into an external resistor (R4), which is not part of the control circuit (10), and from there into the said first terminal (5) of the load (11) by means of the series connection of the independent second adjustable current source (IS4) and the second external electrical resistor (R4), • wherein a first terminal of the second adjustable current source (IS4) is connected to the second output (4) of the control circuit (10) and • wherein the second adjustable power source (IS4) is connected with its second terminal on the other side to the said supply line (1, 2) at low resistance, and • Control of the first output current (I3) and the second output current (I4) by a controller (RG) depending on a measurement parameter (I)3_4 , U I_ist_b ) in such a way that with increasing operating voltage (U) b ) • in a first operating voltage range (A) with a specific magnitude, only the first controllable current source (IS3) delivers a non-zero output current (IS3) and • then in a second operating voltage range (B) immediately adjacent to the first operating voltage range (A) in terms of magnitude, with reference to the operating voltage (U) b ) the second current source (IS4) supplies a non-zero second output current (I4) which increases in magnitude with increasing operating voltage, and the first output current (I3) of the first current source (IS3) is increased by the amount of the value of this second output current (I4) with increasing operating voltage (U). b ) is progressively reduced in amount and • then in an amount proportional to the second operating voltage range (B) relative to the operating voltage (U)b ) immediately adjacent third operating voltage range (C) the second current source (IS4) one from the operating voltage (U b ) provides a second output current (I4) that is independent in magnitude and non-zero, and the first output current (I3) of the first current source (IS3) is negligible in magnitude, but at least less than 1% of the magnitude of the second output current (I4), is characterized by - that by regulating the current, the location where the power loss occurs due to the regulation of the current is also determined by a further control parameter, • that the current magnitude distribution of the sum of the output currents (I3+I4) from the first output current (I3) and the second output current (I4) to the first output current (I3) and the second output current (I4) of the control circuit (10) is determined by at least one control parameter, i.e. a distribution parameter (V) p), is dependent on the control circuit (10) which is determined in the control circuit or specified from the outside via an analog or digital interface (ST) or another signal (PWM). [2] Method according to claim 1 • wherein the sum current (I3+I4, I3+I4+I8) of the output currents (I3, I4, I3) of several current sources (IS3, IS4, IS8) is measured by a sum current measuring device (MI) 3_4 ), in particular a shunt resistance (R mb ), is recorded and • wherein their output signal (I 3_4 and / or U I_ist_b ) as measurement parameters for the independent control of the first output current (I3) and the second output current (I4) via a control signal (U) ctr3 , U ctr4 ) by a controller (RG) depending on this measurement parameter (I 3_4 and / or U I_ist_b ) is used. [3] Method according to claim 1 or 2 • wherein the load voltage is measured by a voltage measuring device (MU3), in particular a voltage divider (R mb1 , R mb2 ), is recorded and • wherein their output signal (U V_ist_b ) as measurement parameters for the independent control of the first output current (I3) and the second output current (I4) via a control signal (U) ctr3 , U ctr4 ) by a controller (RG) depending on this measurement parameter (U V_ist_b ) is used. [4] Method according to one or more of claims 1 to 3 • wherein the total power (P3+P4) is measured by a power measuring device (MP4, MP3), in particular a voltage divider (R mb1 , R mb2 ) and a shunt resistor (R mb ) in conjunction with a multiplier (MUL), is recorded and • wherein their output signal (U P_ist_b) as measurement parameters for the independent control of the first output current (I3) and the second output current (I4) via a control signal (U) ctr3 , U ctr4 ) by a controller (RG) depending on this measurement parameter (U V_ist_b ) is used. [5] Method for the regulated supply of electrical energy to a consumer (11) by means of a control circuit (10), in particular according to one or more of claims 1 to 4, wherein • the control circuit (10) has at least four connections (1, 2, 3, 4, 8), • the consumer (11) has at least two supply connections (5, 6), • the control circuit (10) is supplied with electrical energy from a regulated or unregulated energy source (7) via at least two of its terminals (1, 2), • at least one second output (4) or one third output (8) of the control circuit (10) is electrically connected to at least one first terminal (5) of the load (11) via a second external resistor (R4) that is not part of the control circuit (10) or a third external resistor (R8) that is not part of the control circuit (10), • a first output (3) of the control circuit (10) is electrically connected via a first external resistor (R3) or directly to the said first terminal (5) of the load (11), • the consumer (11) is electrically connected to the energy source (7) or to another connection (2) of the control circuit (10) or to another electrical current source (IS8, IS9) or energy source via at least one further second connection (6), • if at least one first external resistor (R3) and another external resistor (R4, R8) are present and these have different values, • the sum of the output currents (I3+I4, I3+I4+I8) at the outputs (3, 4, 8) of the control circuit (10) as a setpoint (I sum ) specified total current (I3+I4, I3+I4+I8) corresponds to and • the current magnitude distribution of the sum of the output currents (I3+I4, I3+I4+I8) to the output currents (I3, I4, I3) of the outputs (3, 4, 8) of the control circuit (10) of at least one control parameter, i.e. a distribution parameter (V) p ), is dependent on the control circuit (10) determined or specified externally via an analog or digital interface (ST) or another signal (PWM) and • the control is carried out using at least two real current sources (IS3, IS4, IS8) with finite internal resistances that supply the output currents (I3, I4, I8). [6] Method according to claim 1 wherein • where at least one output current (I3, I4, I8) is measured at least temporarily and / or • wherein at least one output voltage (U3, U4, U8) is measured at least temporarily at one of the outputs (3, 4, 8) of the control circuit (10) and / or • where at least one supply voltage (U) b ) a control circuit (10) is measured and / or • wherein at least one output power (P3, P4, P8) is measured at least temporarily at one of the outputs (3, 4, 8) of the control circuit (10) and / or • where at least one temperature (T) is at least temporarily o in the control circuit (10) itself or o in parts of the control circuit (10) or o near the control circuit (10) or o in the vicinity of at least one consumer (11) or o near an external resistor (R3, R4, R8) or o near a control transistor (TR3, TR4, TR s ) or or a power source (IS3, IS4, IS8) nearby or o in a coolant or cooling medium near a resistor (R3, R4, R8) is measured. [7] Method according to one or more of claims 1 to 6 • wherein at least one of the measured values ​​or at least one of the temporarily stored values ​​or at least one of the values ​​derived from these (said values) is compared with at least one target value, • the comparison is made by determining whether the said value is smaller than the target value, larger than the target value, or optionally equal to the target value, where equal to means that the said value lies within a tolerance band around the target value and a said value that lies within this tolerance band is not evaluated as larger or smaller within the framework of the said comparison, • where at least one of the aforementioned values ◯ one of the output currents (I3, I4, I8) or ◯ one of the output voltages (U3, U4, U8) or ◯ one of the output powers (P3, P4, P8) or ◯ the sum of all or part of the output currents (I3+ I4, I8+I9, I 3+ I4+I8, I 3+ I4+I8+I9) or o the sum of all or part of the output outputs (P3+P4, P3+P4+P8) or o the operating voltage (U) provided by the energy source (7) b ) or o the temperature (T) of the control circuit (10) or o the temperature (T) of a part of the control circuit (10) or o the temperature (T) near the control circuit (10) or o the temperature (T) near at least one consumer (11) or o the temperature (T) near at least one external resistor (R3, R4, R8) or o the temperature (T) near at least one control transistor (TR3, TR4, TRs) or o the temperature (T) near at least one power source (IS3, IS4, IS8) or o the temperature (T) in a coolant or cooling medium near a resistor (R3, R4, R8) or o a cached value of these values ​​or o a quantity derived from these values ​​and / or their cached values is. [8] Method according to one or more of claims 1 to 7 wherein • at least one distribution parameter (V p ) ◯ one of the output currents (I3, I4, I8) or o one of the output voltages (U3, U4, U8) or o one of the output services (P3, P4, P8) or o the sum of all or part of the output currents (I3+ I4, I8+I9, I 3+ I4+I8, I3+I4+I8+I9) or o the sum of all or part of the output outputs (P3+P4, P3+P4+P8) or o the operating voltage (U) provided by the energy source (7) b ) or o the temperature (T) of the control circuit (10) or o the temperature (T) of a part of the control circuit (10) or o the temperature (T) near the control circuit (10) or o the temperature (T) near at least one consumer (11) or o the temperature (T) near at least one external resistor (R3, R4, R8) or o the temperature (T) near at least one control transistor (TR3, TR4, TR s ) or o the temperature (T) near at least one power source (IS3, IS4, IS8) or o the temperature (T) in a coolant or cooling medium near a resistor (R3, R4, R8) or o a cached value of the above values ​​or or a quantity derived from these above values ​​or o a quantity derived from cached values ​​of the preceding values. [9] Method according to one or more of claims 1 to 8 wherein • the sum of at least two output currents (I3+I4, I3+I4+I8) depending on ◯ at least one of the output voltages (U3, U4, U8) and / or o at least one of the output services (P3, P4, P8) and / or or the sum of all or part of the output outputs (P3+P4, P3+P4+P8) and / or o the operating voltage (U) provided by the energy source (7) b ) and / or o the temperature (T) of the control circuit (10) and / or o the temperature (T) of a part of the control circuit (10) and / or o the temperature (T) near the control circuit (10) and / or o the temperature (T) in the vicinity of at least one consumer (11) and / or o the temperature near at least one external resistor (R3, R4, R8) and / or o the temperature (T) in a coolant or cooling medium near a resistor (R3, R4, R8) and / or or a cached value of these values ​​and / or or a quantity derived from the above values ​​and / or o one of the sizes derived from the aforementioned values ​​stored in their cache. [10] Method according to one or more of claims 1 to 7 • wherein at least one output current (I4) is regulated to be constant in at least one operating voltage range (C). [11] Method according to one or more of claims 1 to 10 • wherein at least a second output power (P4) of a current source (IS4), which supplies its current (I4) through an external resistor (R4) to the load (11) in at least one operating voltage range (E) with increasing operating voltage (U) b ) sinks and • wherein in this operating voltage range (E) another regulated current source (IS3) also provides a current (I3) which increases with increasing operating voltage (U) b ) increases, delivering an initial output power (P3) to the consumer (11) and • where the sum of the output powers (P3+P4) is kept constant in this operating voltage range (E). [12] Method according to one or more of claims 1 to 10 wherein • at least one current sum (I3+I4, I3+I4+I8) of at least two output currents (I4, I3, I8) is kept constant in at least one operating voltage range (B, C, C1, C2, E) and • at least one of the currents (I4) in at least a second operating voltage range (B) is not constantly regulated in which the said current sum (I3+I4, I3+I4+I8) of at least two output currents (I4, I 3, I8) is kept constant • wherein said second operating voltage range (B) is part of or equal to one of the first-mentioned operating voltage ranges (B, C, C1, C2). [13] Method for the regulated supply of at least two consumers (11_1, 11_2, 11_3) with electrical energy, • wherein at least one part of the consumers (11_1, 11_2, 11_3) is supplied with electrical energy by means of a method according to one or more of claims 1 to 12. [14] Method according to claim 13, • wherein at least two output currents (I3, I4, I8) are each controlled by an external reference signal (I ref_ext_1 , I ref_ext_2 , I ref_ext_3 ) or can be set by programming. [15] Method according to one or more of claims 1 to 14 • where a consumer has at least two connections (5_1, 5_2, 5_3) and • wherein the consumer is supplied with electrical energy via at least two of these connections separately by means of a method according to one of claims 1 to 14.

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