Power transfer systems and methods.

Abstract

A solar panel system for powering an AC or DC load includes multiple photovoltaic cells and corresponding radio frequency power modules that can be phase-locked to the frequency of any AC power signal present at the load. The system or circuit has a single aggregator for collecting either the AC or DC power signals provided by the photovoltaic cells via the radio frequency power modules and an HF link system. Power transmission in the HF link system may be by wire, wireless, or short-range bimodal wireless power transmission. The photovoltaic cells are placed face-down on a planar transparent solar cover, and a printed circuit board with circuitry for the radio frequency power module is attached face-up. The packaged device is conformally encapsulated with a protective polymer cover. A method is provided for encapsulating the photovoltaic cells and their associated radio frequency power modules together on a planar transparent solar cover.

Description

[Technical Field]

[0001] Cross-references to related applications. This application claims priority to and the benefit of U.S. Patent Application No. 63 / 379,547, filed October 14, 2022, and U.S. Application No. 63 / 476,781, filed December 22, 2022, the contents of each of which are incorporated herein by reference in their entirety for all purposes.

[0002] The present invention relates to a power transmitter, receiver, and a system and method for power transmission. [Background technology]

[0003] In inductive power transfer (IPT), power is typically transferred between coils of wire by a magnetic field. An alternating current (AC) is driven through a transmitting coil to generate an oscillating magnetic field. The magnetic field passes through a receiving coil, inducing an AC current in the receiving coil. The induced AC current can either drive a load directly or be rectified to a direct current (DC) that is applied to drive a load. To achieve high efficiency, the transmitter and receiver coils must be in close proximity. For example, it is common for the transmitter and receiver coils to be separated by only a fraction of the coil diameter (e.g., within a centimeter) and for the coil axes to be closely aligned.

[0004] Some IPT systems employ resonant inductive coupling, which can increase efficiency in IPT by using a resonant circuit. Resonant inductive coupling can achieve higher efficiency over greater distances than non-resonant inductive coupling. In resonant inductive coupling, power is transferred between one in the transmitter and one in the receiver by the magnetic field between two resonant circuits. The two circuits are tuned to resonate at the same resonant frequency. Summary of the Invention [Problem to be solved by the invention]

[0005] In some IPT systems, the magnetic field can generate eddy currents in nearby metals, which can cause significant temperature rise and a fire hazard. Ferrite plates can be used to provide shielding and improve inductive coupling, but can increase the cost of such systems.

[0006] Capacitive power transfer (CPT) utilizes an electric field for the transfer of power between two electrodes, such as metal plates. Typically, four metal plates are used in a CPT system to form a capacitive coupler. Two plates are used as power transmitters, and the other two plates act as power receivers, resulting in at least two coupling capacitors providing a power flow loop. An AC voltage is applied to the transmitter plate by the transmitter. The oscillating electric field induces an alternating potential on the receiver plate, which causes an AC current to flow in the load circuit. Resonance can also be used in conjunction with capacitive coupling to extend the range of power transfer.

[0007] In CPT systems, eddy current losses can be reduced and the plates used are low cost, reducing system costs. However, a problem with many systems is that high voltages can be imposed on the plates. These high voltages can generate strong electric fields, resulting in significant field emissions in the surrounding area.

[0008] There are also problems associated with the capacitive or inductive compensation networks in CPT and IPT systems. Currently, both CPT and IPT systems require minimal isolation between the receiver and transmitter. This typically requires large capacitors and inductors in the primary and secondary compensation networks. These large elements are difficult to manufacture, and their parasitic resistance can dramatically reduce system efficiency. Additionally, these compensation elements are not directly involved in the power transfer process.

[0009] There remains a need for wireless power transmitters and receivers with fewer components and / or reduced cost. There remains a need for wireless power transmitters and receivers with reduced reliance on compensation networks. There remains a need for wireless power transmitters and receivers with higher efficiency. There remains a need for wireless power transmitters with more flexible requirements for alignment and spacing therebetween. There is a need for a power transmission system that can transfer power in both forward and reverse directions between a load and a source, including between a DC source and an AC grid.

[0010] The field of power transmission for consumer products is becoming increasingly important, and in the automotive field, wiring harnesses are becoming increasingly important. An expensive subsystem of a vehicle, the market for automotive wiring harnesses is expected to exceed $77 billion US dollars by the end of the current decade. Looking at the gasoline mileage of internal combustion engines, the carbon emissions of these vehicles, and the range of electric vehicles, the cost, weight, and power transfer efficiency of these harnesses have become major concerns in vehicle design. Given that materials and components represent some 57% of vehicle manufacturing costs, the concern can be understood.

[0011] While battery technology has steadily improved to provide batteries with higher energy densities, consumer demand is simultaneously increasing due to the increasing number of auxiliary user electronic devices and electrically powered systems integrated into vehicles. This places even greater demands on the battery, vehicle weight, cost, and power transmission efficiency. High-voltage battery systems have been proposed in the automotive industry since the 1990s, in part in the hope of reducing the weight of wiring harnesses.

[0012] Efforts to reduce the amount of expensive copper employed in wiring harnesses have shifted toward the use of less expensive aluminum. This trend is also driven by the desire to save several 401bs of weight in a typical automobile. This trend toward aluminum has its own problems, due in part to aluminum's 1.58 times higher resistivity compared to copper. Aluminum also suffers from a phenomenon known as creep, which loosens connections. Additionally, aluminum also oxidizes, requiring careful connection considerations. Some aspects of wiring harnesses still require copper, and any connection between copper and aluminum introduces galvanic potential problems.

[0013] There is a need for an alternative approach to vehicle wiring harnesses that reduces expensive copper content, provides flexibility with respect to voltage, avoids the problems presented by aluminum, and reduces weight.

[0014] At the same time, the efficiency of power transmission technology needs to be improved to keep up with rapidly advancing battery technology and accelerate developments in the field of electric vehicles.

[0015] These requirements are not limited to the automotive sector, but also concern, for example, the field of solar energy power transmission, and in some variants also apply to other household appliances such as computer and television displays. Power conditioning units for optimally extracting power from sources with various voltages are widely used today, but they generally suffer from a limited degree of control equipment, which prevents the power transmission efficiency from being optimized.

[0016] The foregoing examples of the related art and limitations associated therewith are intended to be illustrative and not exhaustive. Other limitations of the related art will become apparent to those skilled in the art upon reading this specification and studying the drawings. [Means for solving the problem]

[0017] In a first aspect, a bimodal near-field resonant wireless power transfer system configured for simultaneous capacitive and inductive power transfer according to an adjustable transfer mode ratio at a resonant power signal oscillation frequency is presented, the system comprising: a transmitter subsystem comprising a transmitter antenna subsystem and a power signal tuner module, the tuner module configured to adjust the transfer mode ratio by adjusting a power signal provided to the transmitter antenna subsystem by the tuner module; and a receiver subsystem comprising a receiver antenna subsystem configured to receive power from the transmitter antenna subsystem at the transfer mode ratio.

[0018] The tuner module may be configured to adjust the power signal by adjusting a phase difference between a current and a voltage of the power signal provided to the transmitter antenna subsystem. The transmitter subsystem may further include a controller and at least one sensor, where the controller is configured to receive sensor information from the at least one sensor and automatically provide tuning instructions to the tuner module based on the sensor information, and the tuner module is configured to adjust the phase difference between the current and the voltage of the power signal provided to the transmitter antenna subsystem in accordance with the tuning instructions.

[0019] At least one sensor may be located on the transmitter subsystem. In other embodiments, at least one sensor may be located on the receiver subsystem, and the controller may be configured to wirelessly receive sensor information. The at least one sensor may be one of a power load sensor, a transmit power sensor, and a surrounding object sensor. a detector and a distance detector positioned to detect the distance between the transmitter antenna and the receiver antenna.

[0020] The resonant power signal oscillation frequency may be freely varied within a predetermined frequency band, which may be an industrial, scientific, and medical (ISM) frequency band, and the system may be detuned to an extent that allows the resonant power signal oscillation frequency to vary within opposite limits of the predetermined frequency band.

[0021] In a further aspect, a wireless method is provided for transferring power bidirectionally according to an adjustable transfer mode ratio at a resonant power signal oscillation frequency, the method including: providing a transmitter subsystem including a power signal tuner module and a transmitter antenna subsystem configured to resonate at the resonant power signal oscillation frequency; providing a receiver subsystem including a receiver antenna subsystem configured to resonate at the resonant power signal oscillation frequency; providing a power signal from the tuner module to the transmitter antenna subsystem at the power signal oscillation resonant frequency; adjusting the transmission mode ratio by adjusting the power signal from the tuner module to the transmitter antenna subsystem; and receiving the transmitted power at the receiver subsystem at the power signal oscillation resonant frequency via the receiver antenna subsystem at the transmission mode ratio. Adjusting the transfer mode ratio may include adjusting a phase difference between a current and a voltage of the power signal provided to the transmitter antenna subsystem.

[0022] Providing the transmitter subsystem may further include providing a controller and at least one sensor, and adjusting the phase difference between the current and the voltage may be performed by the tuner module via a command from the controller based on sensor information received from the at least one sensor by the controller. The controller command may be automatically issued to the tuner module upon receipt by the controller of the sensor information, and the tuner module may automatically execute the command from the controller to change the phase difference.

[0023] The method may further include allowing the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an industrial, scientific, and medical (ISM) frequency band. Providing the transmitter subsystem may include providing a transmitter subsystem that is detuned to an extent that allows the resonant power signal oscillation frequency to vary within opposite limits of the predetermined frequency band.

[0024] In a further aspect, a bimodal near-field resonant wireless power transfer system configured for simultaneous capacitive and inductive power transfer is provided according to an adjustable transfer mode ratio of capacitive power transfer to inductive power transfer at a variable resonant power signal oscillation frequency, including: a transmitter subsystem comprising a transmitter antenna and a power signal tuner module, the power signal tuner module adjusting the transfer mode ratio by adjusting a power signal provided to the transmitter antenna subsystem by the power signal tuner module; and a receiver subsystem comprising a receiver antenna subsystem for receiving power from the transmitter antenna at the transfer mode ratio.

[0025] The system communicates information between the transmitter antenna subsystem and the receiver antenna subsystem via the transmitter antenna and the receiver antenna of the receiver antenna subsystem. The system may further include a modulator for modulating the information onto an information-bearing signal and providing the information-bearing signal to the transmitter antenna subsystem. The system may modulate the information onto the information-bearing signal and provide the information-bearing signal to the transmitter antenna subsystem. The modulator may be configured to modulate the information-bearing signal to the transmitter antenna subsystem according to the information. The power signal tuner module may include the modulator.

[0026] The information-bearing signal may have a frequency different from the variable resonant power signal oscillation frequency. The modulator may modulate the information-bearing signal by any one of frequency modulation, amplitude modulation, and phase modulation. The information-bearing signal may be modulated such that the variable power signal oscillation frequency is a harmonic of the frequency of the information-bearing signal. The information-bearing signal may be modulated onto a harmonic of the power signal. The signal modulated and provided to the transmitter antenna subsystem may be the power signal.

[0027] The modulator may transfer information from the receiver antenna subsystem to the transmitter antenna subsystem by modulating a reflective characteristic of the receiver antenna according to the information. The modulated reflective characteristic of the receiver antenna may be the impedance of the receiver antenna.

[0028] The system can transfer information from the receiver subsystem to the transmitter subsystem by modulating the reflection by the receiver antenna of a signal from the transmitter subsystem. The receiver subsystem can modulate the reflection characteristics of the receiver antenna. The receiver subsystem can modulate the impedance of the receiver antenna.

[0029] A power load may be present at the output of the receiver subsystem, and the information may comprise one or more of: presence of the power load, charge level of the power load, power transfer efficiency, charge rate of the power load, state of the power load, presence of voltage across the power load, charge capacity of the power load, and remaining time to charge the power load.

[0030] The system may communicate digital information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The system may communicate analog information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The receiver subsystem may be configured to transmit power to a subsequent receiver subsystem. The receiver may further comprise a rectifier comprising a phase shifter.

[0031] In a further aspect, a bimodal resonant near-field radio frequency power transfer system is provided comprising a plurality of power transmit-receive modules for simultaneous capacitive and inductive power transfer with an adjustable transfer mode ratio via a power signal at a power signal frequency, each of the plurality of power transmit-receive modules in wired communication with a transmitter-receiver resonator arranged to exchange power with at least a different one of the plurality of power transmit-receive modules.

[0032] A first of the plurality of power transmit receive modules may include a power signal tuner module adjustable to change a transfer mode ratio by tuning a power signal provided by the power signal tuner module to a transmitter-receiver resonator in wired communication with the first of the plurality of power transmit receive modules. At least one of the plurality of power transmit receive modules may include a modulator configured to modulate information onto a radio frequency signal exchanged between an associated transmitter-receiver resonator in wired communication with at least one of the plurality of power transmit receive modules and a transmitter-receiver resonator in wired communication with any other of the plurality of power transmit receive modules.

[0033] The modulator may be an amplitude modulator, a frequency modulator, or a phase modulator. The information may include one or both of digital and analog information. The radio frequency signal modulated by the modulator may be a power signal. The radio frequency signal modulated by the modulator may have a frequency different from the power signal frequency. The radio frequency signal modulated by the modulator may have a frequency that is a harmonic of the power signal frequency. The power signal frequency may be a harmonic of the frequency of the modulated signal.

[0034] The modulator may be configured to modulate the reflection characteristics of an associated wired transmitter-receiver resonator in accordance with the information to impose the information on a signal reflected by the wired transmitter-receiver resonator. The modulator may be configured to modulate a signal provided to the associated transmitter-receiver resonator in accordance with the information. The power signal tuner module of a first power transmit-receive module of the plurality of power transmit-receive modules may include a modulator. Each of the power transmit-receive modules may include a compensation network, and the compensation network may include a modulator. At least one of the power transmit-receive modules may include a radio frequency oscillator providing a signal at a power signal frequency to the at least one power transmit-receive module, and the radio frequency oscillator may include a modulator.

[0035] Each of the multiple power transmit / receive modules may be reconfigurable between a power transmitter mode and a power receiver mode. Each of the power transmit / receive modules may include a differential self-synchronous radio frequency power amplifier / rectifier that can be reconfigured between an amplifier condition and a rectifier condition corresponding to the power transmitter mode and the power receiver mode of the power transmit / receive module, respectively. The differential self-synchronous radio frequency power amplifier / rectifier may be a differential switch-mode self-synchronous radio frequency power amplifier / rectifier. Each of the power transmit / receive modules may include a controller, and the reconfiguration may be controlled by the controller. Each differential self-synchronous radio frequency power amplifier / rectifier may include a phase shifter adjustable by the controller to reconfigure the differential self-synchronous radio frequency power amplifier / rectifier between the amplifier condition and the rectifier condition.

[0036] When a power load is present at the output of one of the plurality of power transmission modules in receiver mode, the information may include one or more of: presence of the power load, charge level of the power load, power transfer efficiency, charge rate of the power load, state of the power load, presence of voltage across the power load, charge capacity of the power load, and remaining time to charge the power load.

[0037] In a further aspect, a near-field radio frequency method for transferring power via a power signal at a power signal frequency is provided, the method including providing a bimodal resonant near-field radio frequency power transfer system including a plurality of power transmit-receive modules, each in wired communication with a transmitter-receiver resonator arranged to exchange power with at least one of the plurality of power transmit-receive modules; and operating the power transfer system for simultaneous capacitive power transfer and inductive power transfer according to an adjustable transfer mode ratio.

[0038] A first power transmit-receive module of the provided plurality of power transmit-receive modules may include a power signal tuner module, and operating the power transmission system may include changing a transfer mode ratio by adjusting the power signal tuner module. Providing the power transmission system may include providing at least one power transmit-receive module between the plurality of power transmit-receive modules in wired communication with an associated transmitter-receiver resonator and having a modulator, and operating the power transmission system, and operating the power transmission system may include exchanging radio frequency signals between the associated transmitter-receiver resonator and the transmitter-receiver resonator in wired communication with at least one of the plurality of power transmit-receive modules, and modulating information onto the exchanged radio frequency signals. When a power load is present at an output of one of the plurality of power transmit-receive modules, the information may include, for example, but is not limited to, one or more of: presence of the power load, charge level of the power load, power transfer efficiency, charge rate of the power load, state of the power load, presence of a voltage across the power load, charge capacity of the power load, and remaining time to charge the power load.

[0039] The information may be modulated onto the exchanged radio frequency signals by amplitude modulation, frequency modulation, or phase modulation. Modulating information onto the exchanged radio frequency signals may include modulating digital information or analog information onto the exchanged radio frequency signals.

[0040] Modulating the information onto the exchanged radio frequency signals can include modulating the information onto a power signal. Modulating the information onto the exchanged radio frequency signals can include modulating the information onto a signal having a frequency different from the power signal frequency. Modulating the information onto the exchanged radio frequency signals can include modulating the information onto a signal having a frequency that is a harmonic of the power signal frequency. Modulating the information onto the exchanged radio frequency signals can include modulating the information onto a signal having a harmonic of the power signal frequency.

[0041] Modulating information onto the exchanged radio frequency signals may include modulating according to a reflection characteristic of an associated wired transmitter-receiver resonator to impose information on a signal reflected by the wired transmitter-receiver resonator. Modulating information onto the exchanged radio frequency signals may include modulating according to a signal provided to the associated transmitter-receiver resonator.

[0042] The method may include operating a power signal tuner module of a first power transmit receive module of the plurality of power transmit receive modules to modulate information onto the exchanged radio frequency signal. Each of the provided power transmit receive modules may include a compensation network, and the compensation network may include a modulator, enabling the compensation network to be operated to modulate information onto the exchanged radio frequency signal. At least one of the power transmit / receive modules may include a radio frequency oscillator that provides a signal at the power signal frequency to the at least one power transmit / receive module, and the radio frequency oscillator may include a modulator that allows information to be modulated onto the exchanged radio frequency signal in the oscillator.

[0043] Each of the plurality of power transmit-receive modules may be reconfigurable between a power transmitter mode and a power receiver mode, and the method may further include reconfiguring at least two of the plurality of power transmit-receive modules between a power transmitter mode and a power receiver mode to reverse the direction of power transmission between the at least two transmit-receive modules. Each of the plurality of power transmit-receive modules may include a differential self-synchronous radio frequency power amplifier / rectifier reconfigurable between an amplifier condition and a rectifier condition corresponding to the power transmitter mode and the power receiver mode of the power transmit module, respectively, and the method may include reconfiguring the differential self-synchronous radio frequency power amplifier / rectifier of the at least two transmit-receive modules between the amplifier condition and the rectifier condition. Each differential self-synchronous radio frequency power amplifier / rectifier may include an adjustable phase shifter to reconfigure the differential self-synchronous radio frequency power amplifier / rectifier between the amplifier condition and the rectifier condition, and the method may include adjusting the phase shifter of each of the differential self-synchronous radio frequency power amplifier / rectifier of the at least two transmit-receive modules.

[0044] In a further aspect, a near-field resonant wireless power transfer system is provided, comprising: a plurality of substantially mutually isolated transmitter resonators and a corresponding transmitter module, each transmitter module in power signal communication with a respective transmitter resonator, each transmitter module comprising a transmit controller and a power signal source having a power signal oscillation frequency and a power signal phase, each power signal source controlled by a corresponding transmit controller; one or more receiver subsystems, each having a corresponding receiver resonator; a software lookup table of individual allowable power signal oscillation frequencies for the power signal sources; and software loaded into memory and executed by the controller of any of the transmitter modules to perform the following operations when executed by the controller: measuring one of the input impedance of the corresponding transmitter resonator and a test signal power consumption by the corresponding transmitter resonator; and selecting a frequency from the lookup table based on one of the input impedance of the corresponding transmitter resonator and the test signal power consumption by the corresponding transmitter resonator. When executed, the software may perform operations of measuring a level of power transferred by the corresponding transmitter resonator while adjusting the phase of the power signal from the corresponding power signal source. The transmitter resonators may be substantially separated from one another by a grounded shield grid.

[0045] In a further aspect, a wireless near-field method is provided for transferring power at variable resonant power signal oscillation frequencies from a multi-transmitter subsystem to a single resonant receiver subsystem, the method including providing a multi-transmitter subsystem comprising a plurality of mutually independent transmitter resonators each driven by a corresponding transmitter module that can be independently set to one of a plurality of preset power signal oscillation frequencies in a predetermined frequency band, all of the transmitter resonators having a common transmit plane. the method includes positioning a resonant receiver subsystem, the resonant receiver subsystem including a single receiver resonator overlapping two or more of the transmitter resonators, adjacent a common transmission plane, measuring one of the input impedances of each of the transmitter resonators and one of the powers drawn from a test signal by each of the transmitter resonators, setting a power signal to each of a plurality of mutually independent transmitter resonators based on the corresponding one of the measured resonator input impedances and the power drawn from the test signal by the corresponding transmitter resonator, selecting a power signal oscillation frequency for each active transmitter resonator from among a plurality of preset power oscillation frequencies based on the measured input impedance of the active transmitter resonator, and setting the power signal of each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting a phase of the power signal applied to each corresponding transmitter resonator to a phase at which power transfer through the transmitter resonator is substantially maximum.

[0046] In a further aspect, a wireless near-field method is provided for transferring power from a multi-transmitter subsystem to two or more receiver subsystems at variable resonant power signal oscillation frequencies, the method including providing a multi-transmitter subsystem comprising a plurality of mutually independent transmitter resonators each driven by a corresponding transmitter module independently configurable to one of a plurality of preset power signal oscillation frequencies in a predetermined frequency band, all of the transmitter resonators having a common transmission plane. the method includes positioning two or more resonant receiver subsystems adjacent to a common transmission plane, each having a single receiver resonator overlapping two or more of the transmitter resonators, measuring one of the input impedances of each of the transmitter resonators and one of the powers drawn from a test signal by each of the transmitter resonators, setting a power signal to each of a plurality of mutually independent transmitter resonators based on the corresponding one of the measured resonator input impedances and the power drawn from the test signal by the corresponding transmitter resonator, selecting a power signal oscillation frequency for each active transmitter resonator from among a plurality of preset power oscillation frequencies based on the measured input impedance of the active transmitter resonator, and setting the power signal of each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting a phase of the power signal applied to each corresponding transmitter resonator to a phase at which power transfer through the transmitter resonator is substantially maximum.

[0047] In a further aspect, a short-range wireless system for transferring power from a photovoltaic cell to a power load is provided, the system including: a transmitter module in wired electrical communication with the photovoltaic cell; a transmitter resonator configured to resonate at an oscillation frequency; a receiver resonator resonating at the oscillation frequency and positioned to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; and a receiver module in wired electrical communication with the receiver resonator, the receiver module configured to receive power from the receiver resonator and render the received power in DC form to the power load via the wired electrical communication.

[0048] The transmit module may include a power amplifier configured to modulate power received from the solar cell with an oscillation frequency. The transmit module may include an oscillator configured to provide the oscillation frequency to the power amplifier. The transmit module may include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. The transmit module may include a transmit tuning network configured to vary at least a phase of the power provided by the transmit module to the transmitter resonator under control of the controller based on second information from at least one of the one or more sensors.

[0049] The system may include a power conditioning unit electrically connected between the photovoltaic cell and the transmitter module and configured to adapt power from the photovoltaic cell to a format compatible with the transmitter module. The transmitter module may include small-signal electronics, and the power conditioning unit may be further configured to provide power to the small-signal electronics. The transmitter resonator may be disposed on a surface of the photovoltaic cell facing the active solar radiation-receiving surface of the cell. The transmitter resonator has a surface area that is at least a majority of the extent of the active solar radiation-receiving surface of the cell.

[0050] The transmitter resonator may have a planar area smaller than a planar area of ​​the receiver resonator. The receiver resonator may be positioned and configured to receive power from the further transmitter resonator via at least one of capacitive coupling and magnetic induction at a resonant frequency.

[0051] In a further embodiment of a near-field wireless system for transferring power from an array of photovoltaic cells to a power load, the system includes a first plurality of transmitter modules, each in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module configured to convert power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; and a second plurality of transmitter resonators, each in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and configured to resonate at the oscillation frequency. The power supply includes a single receiver resonator configured to resonate at an oscillation frequency and positioned to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction, and a receiver module in wired electrical communication with the receiver resonator, the receiver module configured to receive power from the receiver resonators and render the received power in direct current form to a power load via the wired electrical communication.

[0052] Each transmitter module from the first plurality of transmitter modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at an oscillation frequency. Each transmitter module from the first plurality of transmitter modules may include an oscillator configured to provide an oscillation frequency to a corresponding power amplifier. Each transmitter module from the first plurality of transmitter modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmitter module from the first plurality of transmitter modules may include a transmit tuning network configured to change at least a phase of the power provided by the transmitter module to a corresponding transmitter resonator based on second information from at least one of the one or more sensors under control of the corresponding controller.

[0053] The system may include a third plurality of power conditioning units, each power conditioning unit electrically connected between a corresponding photovoltaic cell and a corresponding transmitter module and configured to adapt power from the corresponding photovoltaic cell to a format compatible with the corresponding transmitter module. Each transmitter module from the first plurality of transmitter modules may include small-signal electronic circuitry, and the corresponding power conditioning unit may be further configured to provide power to the small-signal electronic circuitry. Each transmitter resonator from the second plurality of transmitter resonators may be positioned on a surface of a corresponding photovoltaic cell facing the active solar radiation receiving surface of the cell.

[0054] In a further embodiment of a near-field wireless system for transferring power from an array of photovoltaic cells to a power load, the system includes a first plurality of transmitter modules, each in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module configured to convert power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and configured to resonate at the oscillation frequency; a third plurality of receiver resonators configured to resonate at the oscillation frequency; and a fourth plurality of receiver modules, each in wired electrical communication with a corresponding receiver resonator from the third plurality of receiver resonators, configured to receive power from the corresponding receiver resonator and render the received power in DC form to the power load via wired electrical communication.

[0055] Each transmitter module from the first plurality of transmitter modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at an oscillation frequency. Each transmitter module from the first plurality of transmitter modules may include an oscillator configured to provide an oscillation frequency to a corresponding power amplifier. Each transmitter module from the first plurality of transmitter modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmitter module from the first plurality of transmitter modules may include a transmit tuning network configured to change at least a phase of the power provided by the transmitter module to a corresponding transmitter resonator based on second information from at least one of the one or more sensors under control of the corresponding controller.

[0056] The system may further include a fifth plurality of power conditioning units, each power conditioning unit of the fifth plurality of power conditioning units electrically connected between a corresponding photovoltaic cell from the array of solar cells from the first plurality of transmitter modules and a corresponding transmitter module and configured to adapt power from the corresponding photovoltaic cell to a format compatible with the corresponding transmitter module. Each transmitter module from the first plurality of transmitter modules may include small-signal electronic circuitry, and a corresponding power conditioning unit from the fifth plurality of power conditioning units may be further configured to provide power to the small-signal electronic circuitry. Each transmitter resonator from the second plurality of transmitter resonators may be positioned on a surface of a corresponding photovoltaic cell from the array of photovoltaic cells facing the active solar radiation receiving surface of the cell.

[0057] In a further embodiment, a near-field wireless system for transferring power from an array of solar cells to a power load is presented, the system comprising: a first plurality of transmitter modules, each in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module configured to convert power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and configured to resonate at the oscillation frequency; and a third plurality of receiver resonators, each fewer in number than the plurality of transmitter resonators, configured to resonate at the oscillation frequency; each receiver resonator positioned to receive power from a portion of the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction, each receiver module in wired electrical communication with a corresponding receiver resonator, configured to receive power from the corresponding receiver resonator and render the received power in direct current form via wired electrical communication to the power load.

[0058] Each transmitter module from the first plurality of transmitter modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at an oscillation frequency. Each transmitter module from the first plurality of transmitter modules may include an oscillator configured to provide and an oscillation frequency to a corresponding power amplifier. Each transmit module from the first plurality of transmit modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmit module from the first plurality of transmit modules may include a transmit tuning network configured to change at least a phase of the power provided by the transmit module to a corresponding transmitter resonator based on second information from at least one of the one or more sensors under control of the corresponding controller.

[0059] The system may include a fifth plurality of power conditioning units, each power conditioning unit of the fifth plurality of power conditioning units electrically connected between a corresponding photovoltaic cell from the array of solar cells from the first plurality of transmitting modules and a corresponding transmitting module, and configured to adapt power from the corresponding photovoltaic cell to a format compatible with the corresponding transmitting module.

[0060] Each transmitter module from the first plurality of transmitter modules may include small signal electronic circuitry, and a corresponding power conditioning unit from the fifth plurality of power conditioning units may be further configured to provide power to the small signal electronic circuitry. Each transmitter resonator from the second plurality of transmitter resonators may be positioned on a surface of a corresponding photovoltaic cell from the array of photovoltaic cells facing the active solar radiation receiving surface of the cell.

[0061] In a further aspect, a method for transferring power from a solar cell to a power load is provided, the method including converting power from the solar cell into an oscillating power signal having an oscillation frequency in a transmitter module; transferring the power to a transmitter resonator in wired electrical communication with the transmitter module and configured to resonate at the oscillation frequency; receiving the power at a receiver resonator configured to resonate at the oscillation frequency and positioned to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving the power at a receiver module in wired electrical communication with the receiver resonator; and rendering the received power in direct current form to the power load via wired electrical communication.

[0062] In a further embodiment of a method for transferring power from an array of photovoltaic cells to a power load, the method includes converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmitter modules; transferring the power in each of the transmitter modules to a corresponding transmitter resonator from among a second plurality of transmitter resonators configured to resonate at the oscillation frequency; receiving the power at a receiver resonator configured to resonate at the oscillation frequency and positioned to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; receiving the power at a receiver module in wired electrical communication with the receiver resonator; and rendering the received power via the wired electrical communication to the power load in DC form.

[0063] In a further embodiment of a method for transferring power from an array of photovoltaic cells to a power load, the method includes converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmit modules; transferring power to a corresponding transmitter resonator from a second plurality of transmitter resonators, each transmitter resonator configured to resonate at the oscillation frequency; receiving power from each transmitter resonator in a corresponding receiver resonator configured to resonate at the oscillation frequency, each receiver resonator further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving power from each receiver resonator in a corresponding receiver module in wired electrical communication with the receiver resonator; and rendering the received power in direct current form via wired electrical communication to the power load.

[0064] In a further embodiment of a method for transferring power from an array of photovoltaic cells to a power load, the method includes converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmitter modules; transferring power to a transmitter resonator from among a second plurality of transmitter resonators, each of which is configured to resonate at the oscillation frequency; and receiving power from each of the transmitter resonators in any of a third plurality of adjacent receiver resonators, each of which is configured to resonate at the oscillation frequency, each receiver resonator being further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction. Sharing the received power among the third plurality of receiver resonators; and rendering the received power in direct current form from one or more of the third plurality of receiver resonators via wired electrical communication to the power via the corresponding one or more receiver modules. The method may further include converting the voltage and current of the power from each photovoltaic cell to a voltage and current compatible with the corresponding transmitter module before converting the power to the oscillating power signal.

[0065] A power transfer system is provided for supplying power from a DC power source to a power load, the system including a radio frequency power amplifier in wired electrical communication with the power source and configured to convert a DC voltage from the source into an AC voltage signal having an oscillating frequency; a rectifier configured to receive the transferred power from the amplifier; and a receiver controller in communication with the rectifier, the receiver controller configured to adjust the efficiency of the power transfer from the amplifier to the rectifier by adjusting the current-voltage phase characteristic of the rectifier. The rectifier may be a differential self-synchronous radio frequency rectifier.

[0066] The receiver controller may be configured to automatically adjust the current-voltage phase characteristics of the rectifier. The power transfer system may further include a load management system in wired communication with the load and the power disposed between the load and the rectifier, the load management system being configured to increase efficiency of the power transfer by adjusting the input impedance of the rectifier. The management system may be configured to automatically adjust the current-voltage phase characteristics of the rectifier.

[0067] The power transfer system may further include a transmitter controller in communication with the amplifier, the transmitter controller configured to increase efficiency of power transfer by adjusting a current-voltage phase characteristic of the amplifier. The transmitter controller may be configured to automatically adjust the current-voltage phase characteristic of the amplifier to increase efficiency of power transfer.

[0068] The power transfer system may further include an oscillator in communication with the amplifier and a transmitter controller, the transmitter controller being configured to adjust an oscillation frequency via the oscillator.

[0069] The power amplifier can be in direct wired radio frequency communication with the adjustable phase radio frequency rectifier. The power amplifier can be in wireless near-field radio frequency communication with the adjustable phase radio frequency rectifier. The power transfer system can include a transmitter resonator in wired radio frequency communication with the power amplifier and a receiver resonator in wired radio frequency communication with the rectifier. The transmitter resonator and receiver resonator can be in wireless near-field radio frequency communication with each other. The power amplifier can be in at least one of capacitive near-field wireless and inductive near-field wireless radio frequency communication with the rectifier. The power amplifier can be in bimodal near-field wireless radio frequency communication with the rectifier.

[0070] The DC current source may comprise a rechargeable battery, and the load may comprise an electric motor. The load may comprise a computer monitor. The resonant structure of the system may comprise at least one electrically conductive mechanical load-supporting structural component of the system.

[0071] The system may further include a power conditioning unit electrically disposed between the power source and the power transfer system, the power conditioning unit configured to adjust at least one of the current and voltage from the source to improve efficiency of the power transfer.

[0072] A method for power transfer from a DC power source to a power load is also provided, the method including providing a power transfer system in wired electrical communication with the power source, the power transfer system including a high frequency power amplifier in radio frequency communication with an adjustable phase radio frequency rectifier in wired electrical contact with the power load; converting a DC power signal to a DC power signal in the rectifier; and adjusting the efficiency of the power transfer by adjusting the current-voltage phase characteristic of the rectifier. Providing the adjustable phase radio frequency rectifier may include providing a differential self-synchronous radio frequency rectifier.

[0073] The method may further include adjusting the efficiency of the power transfer by adjusting the DC equivalent input resistance of the amplifier. Providing a power transfer system may include providing a load management system in wired communication between the rectifier and the load. Adjusting the DC equivalent input resistance of the amplifier may include adjusting the input impedance of the rectifier by adjusting the load management system. Adjusting the load management system may include automatically adjusting the load management system.

[0074] The method may further include adjusting efficiency of power transfer by adjusting a current-voltage phase characteristic of the power amplifier. Providing a power transmission system may include providing a transmitter controller in communication with the power amplifier to control the power amplifier. Adjusting the current-voltage phase characteristic of the power amplifier may be performed by the transmitter controller. Adjusting the current-voltage phase characteristic of the power amplifier may be performed automatically by the transmitter controller.

[0075] The method may further include adjusting the efficiency of the power transfer by changing the oscillation frequency of the power amplifier.

[0076] Providing a power transfer system may include providing a receiver controller in communication with the rectifier to control the rectifier. Adjusting the current-voltage phase characteristic of the rectifier may be performed by the receiver controller. Adjusting the current-voltage phase characteristic of the rectifier may be performed automatically by the receiver controller.

[0077] Providing the power transfer system can include providing a power amplifier in direct wired radio frequency communication with an adjustable phase radio frequency rectifier. Providing the power transfer system can include providing a power amplifier in wireless short-range radio frequency communication with the adjustable phase radio frequency rectifier.

[0078] Providing the power transfer system may include providing a transmitter resonator in wired radio frequency communication with a power amplifier and a receiver resonator in wired radio frequency communication with a radio frequency rectifier. The method may further include operating the transmitter resonator and the receiver resonator in wireless near-field radio frequency communication. Providing the power transfer system may include providing the power amplifier in at least one of capacitive near-field wireless and inductive near-field wireless radio frequency communication with the rectifier. Providing the power transfer system may include providing the power amplifier in bimodal wireless near-field communication with the rectifier.

[0079] The method may further include providing a power conditioning unit electrically disposed between the power source and the power transfer system, and adjusting the power conditioning unit to adjust at least one of the current and voltage from the power source to improve efficiency of the power transfer.

[0080] There is also provided a method for transmitting power from a DC power source to a power load, the method including providing a power transmission system in wired electrical communication with the power source, the power transmission system including an oscillator capable of oscillating at an oscillation frequency; a power amplifier in wired electrical communication with the power load; a load management system in wired electrical communication with the power load, converting power from the power source into an oscillating power signal having an oscillation frequency at the power amplifier, and, under control of a transmitter controller, transmitting the power signal from the power amplifier through a transmitter tuning network and a load management system in wired electrical communication with the power load. a receiver tuning network, adjusting at least one of the oscillation frequency, the input DC equivalent resistance of the power amplifier, the transmitter tuning network, the receiver tuning network, and the load management system to change the rate of power transmission, and rendering the power received by the load management system in DC form via wired electrical communication to the power load.

[0081] Transferring the power signal through the transmitter tuning network and the receiver tuning network may include transferring power by wired communication. Transferring the power signal through the transmitter tuning network and the receiver tuning network may comprise transferring power by wireless communication. Transferring power by wireless communication may include transferring power by near field communication. Transferring power by close proximity communication may include transferring power by at least one of capacitive coupling and inductive coupling.

[0082] Transferring power from a DC power source can include transferring power from at least one solar cell. Transferring power from a DC power source can include transferring power from at least one solar battery. Transferring power from a DC power source can include transferring power from a power source having a fluctuating voltage.

[0083] In another embodiment, an electrically powered system includes a mechanical load-bearing structure having an electrically conductive first portion, a power load, and a power transfer system including at least one radio frequency resonator configured for near-field wireless power transfer, the resonator having an at least partially electrically conductive first portion. The power supply system may further include a rechargeable battery, and the power load may include an electric motor. The electrically powered system may be an electric vehicle, and the mechanical load-bearing structure may include a chassis of the vehicle. The electrically powered system may be a display monitor, and the mechanical load-bearing structure may be at least one of a frame and a base of the monitor.

[0084] The power supply system may further include a power source. The power transmission system may include a high frequency power amplifier in wired electrical communication with the power source and configured to convert a direct current voltage from the source into an alternating current voltage signal having an oscillation frequency; a rectifier configured to receive the transmitted power from the amplifier; and a receiver controller in communication with the rectifier, the receiver controller configured to adjust the efficiency of the power transfer from the amplifier to the rectifier by adjusting the current-voltage phase characteristic of the rectifier.

[0085] In another embodiment, an apparatus includes a mechanical load-bearing structure having an electrically conductive first portion; a power source; a power load; a power transfer system including a radio frequency power amplifier in wired electrical communication with the power source and configured to convert a direct current voltage from the source into an alternating current voltage signal having an oscillation frequency; a rectifier configured to receive power transferred from the amplifier; and a receiver controller in communication with the rectifier, the receiver controller configured to adjust the efficiency of power transfer from the amplifier to the rectifier by adjusting a current-voltage phase characteristic of the rectifier, wherein the electrically conductive first portion is configured to carry a radio frequency signal in at least one of the amplifier and the rectifier.

[0086] The apparatus may further include a load management system in wired communication with the load and power disposed between the load and the rectifier, the load management system configured to increase efficiency of power transfer by adjusting an input impedance of the rectifier. The apparatus may further include a transmitter controller in communication with the amplifier, the transmitter controller configured to increase efficiency of power transfer by adjusting a current-voltage phase characteristic of the amplifier. The apparatus may further include an oscillator in communication with the amplifier and the transmitter controller, the transmitter controller configured to adjust an oscillation frequency via the oscillator.

[0087] The power amplifier may be in direct wired radio frequency communication with the rectifier via the conductive first portion. The power amplifier may be wireless. The power transfer system may include a transmitter resonator in wired radio frequency communication with a power amplifier and a receiver resonator in wired radio frequency communication with the rectifier, wherein one of the transmitter resonator and the receiver resonator may include a conductive first portion. The transmitter resonator and the receiver resonator may be in wireless near-field radio frequency communication with each other. The power amplifier may be in at least one of capacitive near-field wireless and inductive near-field wireless radio frequency communication with the rectifier. The power amplifier may be in bimodal near-field wireless radio frequency communication with the rectifier. The direct current source may include a rechargeable battery, and the load may include an electric motor.

[0088] In some embodiments, the sealed bidirectional power transfer circuit device includes a plurality of terminals arranged for electrical communication with devices external to the sealed device, the sealed device having at least one DC terminal, at least one AC terminal, and at least one control terminal within the sealed interior, the multi-terminal power switching device being adjustable between an amplification condition and a rectification condition and configured to bidirectionally communicate a DC voltage and a DC current via the at least one DC terminal; and bidirectionally communicate, via the at least one AC terminal, a radio frequency power signal having an amplitude, frequency, and phase in wired data communication with a phase, frequency, and duty cycle adjustment circuit in wired electrical communication with the power switching device via the at least one control terminal, the radio frequency power signal having an amplitude, frequency, and phase in wired data communication with the phase, frequency, and duty cycle adjustment circuit in wired electrical communication with the power switching device via the at least one control terminal, configured to: establish, at the at least one control terminal of the power switching device, a radio frequency oscillating signal having a frequency and phase of the radio frequency power signal; and adjust the power switching device between the amplification condition and the rectification condition by adjusting the phase of the radio frequency oscillating signal under command of the controller. In some embodiments, the controller may be located within the sealed interior of the sealed bidirectional power transfer circuit device. The terminals of the encapsulated power transmission circuit device may include terminals for data communication between the controller and a device external to the encapsulated interior.

[0089] The radio frequency power signal may have a duty cycle and the phase, frequency, and duty cycle adjustment circuit may be further configured to adjust the duty cycle of the radio frequency power signal by adjusting the duty cycle of the radio frequency oscillating signal. The phase, frequency, and duty cycle adjustment circuit may include a radio frequency oscillator for generating the radio frequency oscillating signal under command from the controller.

[0090] The sealed power transmission circuit device may further include a tuning network in wired electrical communication with the power switching device via at least one AC terminal within the sealed interior in wired data communication with the controller, the tuning network configured to condition the radio frequency power signal into a tuned radio frequency power signal under instructions from the controller. The bidirectional power transfer circuit device may include a modulator configured to modulate information onto the radio frequency power signal. The modulator may include a tuning network. The modulator may be configured to modulate the radio frequency power signal with information provided by the controller. The tuning network may include a harmonic termination network circuit configured to suppress harmonics of the radio frequency oscillation signal in the radio frequency power signal. The harmonic termination network may include one or more inductors and one or more of a first harmonic termination, a second harmonic termination, and a third harmonic termination. The sealed power transmission circuit device may further comprise within the sealed interior an amplitude / frequency / phase detector disposed in wired electrical communication with the tuning network and in wired data communication with the tuning network, the amplitude / frequency / phase detector configured to determine the amplitude, frequency, and phase of any radio frequency power signal communicated between the tuning network and an AC load / source external to the sealed device. The tuning network may further comprise one or more of a compensation network, a matching network, and a filter.

[0091] The phase, frequency, and duty cycle adjustment circuit may be configured to receive instructions from the controller based on measurement data communicated to the controller by the amplitude / frequency / phase detector. The phase, frequency, and duty cycle adjustment circuit may be configured to adjust the radio frequency oscillation signal based on feedback signals received directly from the amplitude / frequency / phase detector. The tuning network may include a voltage / current tuner for adjusting the phase difference between the voltage and current of the tuned radio frequency power signal based on measurement data from the amplitude / frequency / phase detector when the power switching device is in an amplification state.

[0092] The sealed power transfer circuit device may further comprise a power management circuit within its sealed interior in wired electrical communication between the power switching device and the external DC power source / load, arranged for impedance matching between the power switching device and the external DC power source / load, for adjusting the DC power communicated between the power switching device and the DC power source / load based on feedback signals received directly from the amplitude / frequency / phase detector. In other embodiments, the sealed power transfer circuit device may further comprise a power management circuit in wired data communication with the controller, arranged in wired electrical communication between the power switching device and the external DC power source / load for impedance matching between the power switching device and the external DC power source / load, for adjusting the DC power communicated between the power switching device and the DC power source / load based on measurement data communicated to the controller by the amplitude / frequency / phase detector.

[0093] The sealed power transmission circuit device may further include a voltage / current detector disposed within the sealed interior in wired data communication with the controller for determining DC voltage and DC current flowing between the power switching device and the power management circuit. The phase, frequency, and duty cycle adjustment circuit may be configured to receive instructions from the controller based on measurement data communicated to the controller by the voltage / current detector. In other embodiments, the phase, frequency, and duty cycle adjustment circuit may be configured to adjust the radio frequency oscillation signal based on feedback signals received directly from the voltage / current detector.

[0094] The sealed power transfer circuit device may further comprise a memory in wired data communication with the controller using an amplitude / frequency / phase detector and a voltage / current detector, the memory configured to receive and store measurement data from the two detectors and provide signal data from the two detectors to the controller.

[0095] The sealed power transmission circuitry may further comprise a power management circuit within the sealed interior in wired electrical communication between the power switching device and an AC power source / load external to the sealed device, configured to match the amplitude, frequency, and phase of the power switching device with the external AC power source / load and to adjust the AC power communicated between the power switching device and the AC power source / load based on feedback signals received directly from the amplitude / frequency / phase detector.

[0096] The enclosed power transmission circuitry may further include a power management circuit in wired data communication with the controller and configured in wired electrical communication between the power switching device and the external AC power source / load to match amplitude, frequency, and phase between the power switching device and the external AC power source / load and to adjust the AC power communicated between the power switching device and the AC power source / load based on measurement data communicated to the controller by the amplitude / frequency / phase detector.

[0097] The sealed power transmission circuit device may further include a voltaic / current detector positioned within the sealed interior in wired data communication with the controller to determine DC voltage and DC current flowing between the power switching device and the power management circuit.

[0098] In some embodiments, the phase, frequency, and duty cycle adjustment circuit is configured to receive instructions from the controller based on measurement data communicated to the controller by the voltage / current detector. In some embodiments, the phase, frequency, and duty cycle adjustment circuit is configured to adjust the radio frequency oscillation signal based on a feedback signal received directly from the voltage / current detector.

[0099] The sealed power transfer circuit device may further include within its sealed interior a memory in wired data communication with the controller using amplitude / frequency / phase detectors and voltage / current detectors, the memory configured to receive and store measurement data from the two detectors and provide signal data from the two detectors to the controller.

[0100] The sealed power transmission circuit device may further include, within its sealed interior, at least one of Bluetooth® communication circuitry, WiFi communication circuitry, Zigbee® communication circuitry, and cellular communication technology circuitry for communicating information between devices external to the sealed power transmission circuit device. The communication circuitry is capable of bidirectional wired communication with at least one communication antenna configured to communicate with devices external to the sealed power transmission circuit device. The antenna for the communication circuitry may be disposed within the sealed interior of the sealed device.

[0101] The bidirectional power transfer circuit device may include a modulator configured to modulate information onto at least one of a radio frequency power signal and a DC voltage. The modulator may include a power switching device. The modulator may be configured to modulate at least one of the radio frequency power signal and the DC voltage with information provided by the controller. The modulator may further include phase, frequency, and duty cycle adjustment circuitry.

[0102] In some embodiments, all of the circuit elements of the bidirectional power transfer circuit device may be monolithically integrated on a silicon single crystal wafer, hi some embodiments, at least a portion of the circuit elements of the device may be integrated by flip-chip technology.

[0103] In one particular embodiment, the electronic circuitry of the encapsulated bidirectional power transmission circuit device may be implemented within a single silicon monocrystalline wafer in conjunction with at least one photovoltaic cell acting as a DC source / load. In a further embodiment, the electronic circuitry of the encapsulated bidirectional power transmission circuit device may be implemented within a single silicon monocrystalline wafer together with at least one photovoltaic cell acting as a DC source / load 700 and a resonator structure acting as an AC load / source on the surface of the silicon monocrystalline wafer. Antennas for use with Bluetooth®, WiFi, Zigbee®, and cellular technologies may be integrated onto the same single silicon monocrystalline wafer.

[0104] In another aspect, a power transfer system for transferring power between a DC source and a variable load is provided. First and second self-synchronous radio frequency rectifier / amplifiers are configured to extract first and second radio frequency (HF) power signals from the DC source at first and second HF frequencies, respectively. An HF power link system is configured to receive and mix the first and second HF power signals to generate a transferred power signal. Power signal conversion circuitry in communication with the HF power link system and the variable load is configured to generate an output power signal from the transferred power signals and provide the output power signal to the variable load.

[0105] The power transfer system further comprises an HF switching signal generator configured to provide first and second switching signals at respective first and second HF frequencies to the first and second rectifier / amplifiers and to establish and control a mutual phase relationship between the first and second switching signals.

[0106] The power signal conversion circuit comprises a switch mode rectifier configured to receive a transferred power signal from the HF power link system and rectify the transferred power signal to generate a rectified power signal, and a unfolding circuit configured to receive the rectified power signal from the switch mode rectifier and unfold the rectified power signal to generate an output power signal.

[0107] The first and second self-synchronous radio frequency rectifier / amplifiers may be configured to operate in a rectification mode, and the switch mode rectifier may be configured to operate in a always-on mode, thereby allowing power to be extracted from a variable load and transferred to a DC source via a power signal conversion circuit and an HF power link system.

[0108] The deployment circuit may be configured to receive a reference signal from the variable load and deploy a rectified power signal synchronously with the signal at the variable load. The power signal conversion circuit, the HF power link system, and the multiple pairs of self-synchronizing radio frequency rectifier / amplifiers may be configured to communicate control information from the rest of the system to the HF switching signal generator. The system may further include one or more controllers configured to communicate data with and control multiple elements of the system. The system may further include an isolatable load information circuit configured to communicate information regarding at least one of the DC level, frequency, and phase of the power signal at the variable load to the HF switching signal generator. The load information circuit may include a phase-locked loop. The load information circuit may further include an isolator system that may include an air gap. The HF power link system may include a wireless power link system, which may be a bimodal wireless HF power link system. The HF power link system may include a wired power link system.

[0109] In two phase-difference-based implementations, the first and second HF frequencies may be the same frequency, and the first and second switching signals may have a mutual phase difference adjustable by the HF switching signal generator. In the first phase-difference-based implementation, the HF switching signal generator is configured to adjust the mutual phase difference between the first and second switching signals based on a DC level at the variable load, thereby generating a transmitted power signal from the HF power link system as a DC signal with a correspondingly adjusted amplitude. In the second phase-difference-based implementation, the HF switching signal generator is configured to modulate the mutual phase difference between the first and second switching signals at a phase modulation frequency derived from the frequency of the power signal at the variable load, thereby generating a transmitted power signal from the HF power link system as an AC power signal modulated at the frequency of the power signal at the variable load.

[0110] In a frequency difference-based implementation, the first and second HF frequencies differ by a difference frequency Af. In this embodiment, the HF switching signal generator is configured to determine the first and second HF frequencies and set the difference frequency Af to twice the frequency of the power signal at the variable load. The HF power link system is configured to generate a transferred power signal at the difference frequency Af, and the power signal conversion circuit is configured to provide an output power signal to the variable load at the frequency of the power signal at the variable load.

[0111] In a further aspect, a method for transferring power between a DC source and a variable load is provided, the method including extracting from the DC source first and second radio frequency (HF) power signals at corresponding first and second HF frequencies via corresponding first and second self-synchronizing radio frequency rectifier / amplifiers; receiving and mixing the first and second HF power signals at an HF power link system to generate a forwarded power signal; power signal conversion circuitry in communication with the HF power link system; and a variable load generating an output power signal from the forwarded power signals and supplying the output power signal to the variable load.

[0112] The method may further include generating in an HF switching signal generator and communicating first and second switching signals at respective first and second HF frequencies to first and second rectifier / amplifiers, and establishing and controlling in the HF switching signal generator a mutual phase relationship between the first and second switching signals. The method may further include receiving and rectifying a transferred power signal from an HF power link system in a switch-mode rectifier of the power signal conversion circuit, and receiving and developing the rectified power signal from the switch-mode rectifier in a development circuit of the power signal conversion circuit. The method may further include setting the first and second self-synchronous radio frequency rectifier / amplifiers to a rectification mode, setting the switch-mode rectifier to an always-on mode, extracting power from a variable load, and transferring the extracted power to a DC source via the power signal conversion circuit and the HF power link system.

[0113] The method may further include developing a rectified power signal synchronous with the signal at the variable load based on a reference signal from the variable load; communicating control information from the rest of the system to the HF switching signal generator via the power signal conversion circuit, the HF power link system, and the first and second self-synchronizing radio frequency rectifiers / amplifiers; controlling multiple elements of the system with one or more controllers in data communication with the multiple elements, and communicating information regarding at least one of the DC level, frequency, and phase of the power signal at the variable load to the HF switching signal generator using an isolatable load information circuit including a phase-locked loop and an optional isolator system. Transferring the power signal in the HF power link system may include transferring the power signal wirelessly, bimodal wirelessly, and wired.

[0114] Two methods for transferring power from a DC source to a variable load employ a phase difference between the switching signals. In these implementations, the first and second switching signals may have the same frequency and a mutual phase difference that can be adjusted by an HF switching signal generator. The method for the first of these implementations includes the following: and adjusting the mutual phase difference between the first switching signal and the second switching signal based on the DC level at the variable load to generate the transmitted power signal from the HF power link system as a DC signal with an amplitude adjusted accordingly.A second method of these implementations includes modulating the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from the frequency of the power signal at the variable load to generate the transmitted power signal from the HF power link system as an AC power signal modulated at the frequency of the power signal at the variable load.

[0115] A method for a frequency difference-based implementation includes determining first and second HF frequencies of corresponding first and second switching signals and setting a difference frequency equal to twice the frequency of a power signal at a variable load. The method further includes generating a transferred power signal from the HF power link system at the difference frequency and providing an output power signal to the variable load at the frequency of the power signal at the variable load.

[0116] A power transfer system that transfers either AC or DC power from a DC source to a variable load using either a phase or frequency difference between switching signals supplied to a pair of self-synchronizing radio frequency rectifier / amplifiers can be extended to transfer power from a single DC source to a single variable load through multiple pairs of rectifier / amplifiers, and to transfer power from multiple DC sources to a single variable load using multiple pairs of rectifier / amplifiers. Apparatus and methods for achieving these ends are described. These apparatus and methods in some implementations also enable the simultaneous transfer of DC and AC power to a load.

[0117] In one aspect, a system is presented for transferring power from at least one DC power source to a variable load, the system including corresponding radio frequency power modules and a single aggregator configured to receive through all of the at least one radio frequency power module power from the corresponding at least one DC power source. Each of the at least one radio frequency power modules may include both an HF switching signal generator and a pair of differential self-synchronous radio frequency rectifier / amplifiers. The pair of rectifier / amplifiers is in wired electrical communication with a DC power source corresponding to the at least one radio frequency power module and is configured to extract power from the corresponding DC power source. The HF switching signal generator can be configured to provide switching signals to the corresponding pair of differential self-synchronous radio frequency rectifier / amplifiers.

[0118] All the high frequency power modules may be phase locked to each other via a phase locked loop to the AC power signal at the variable load. The phase locked loop may be built into the corresponding high frequency power module.

[0119] Each of the at least one radio frequency power module may be in wired electrical communication with both of the differential self-synchronous radio frequency rectifier / amplifiers to receive, mix, and transmit power signals from the two differential self-synchronous radio frequency rectifier / amplifiers. Each of the at least one radio frequency power module may include a switch-mode rectifier in wired electrical communication with the HF link, the switch-mode rectifier arranged and configured to receive and rectify the mixed power signal and transmit based on the rectified power signal. Each of the at least one radio frequency power module may include a deployment circuit arranged and configured to receive the rectified power signal from the switch-mode rectifier, deploy the rectified signal, and transmit via wire based on the deployed power signal.

[0120] The system may include a bimodal wireless near-field HF link system, with each of at least one high frequency power module comprising one primary side of the HF link system in wired electrical communication with both differential self-synchronous radio frequency rectifier / amplifiers in the at least one high frequency power module. The system may include a single collective secondary side of the HF link system configured to receive power from all of the at least one HF link primary sides, the secondary side comprising a single receiver resonator and a single receiver module. The receiver module may be included in the aggregator along with a switch-mode rectifier and a deployment circuit, the switch-mode rectifier being in wired electrical communication with the receiver module and the deployment circuit to receive and rectify the combined power signal from the receiver resonator, and the deployment circuit being in wired electrical communication with the junction unit and configured to receive and deploy the rectified power signal from the rectifier to provide to the variable load. The switching signals provided by the HF switching signal generator to the two differential self-synchronous radio frequency rectifier / amplifiers may differ by one of a predetermined frequency difference and a predetermined phase difference. The system can include a controller configured to communicate at least one of a frequency and a phase determined by the controller based on information about the load and information about the DC source to the HF switching signal generator. The high frequency power module may include the controller.

[0121] In some embodiments, the at least one DC source may be a photovoltaic cell, and the system may include a planar transparent solar cover having planar first and second solar cover surfaces and a frame for mounting the transparent solar cover, with the at least one photovoltaic cell disposed on the first solar cover surface with the planar light-sensitive surface of the at least one photovoltaic cell facing the first solar cover surface. Each radio frequency power module may include radio frequency power circuitry on a printed circuit board in wired electrical communication with the corresponding at least one photovoltaic cell. The radio frequency power circuitry may be disposed on a planar surface of the printed circuit board facing away from the first solar cover surface.

[0122] The system may include a conformal encapsulation layer coupled to the first solar cover surface and covering the at least one photovoltaic cell and the corresponding radio frequency power module. The system may further include a dielectric protective cap on the radio frequency power circuit. The protective cap may be disposed above or below the conformal encapsulation layer. A periphery of the protective cap may be disposed below the conformal encapsulation layer with the protective cap protruding through the conformal encapsulation layer.

[0123] The printed circuit board may be disposed adjacent to the corresponding at least one photovoltaic cell. In some implementations, the printed circuit board may be disposed on an insulating layer disposed on a back surface of the photovoltaic cell. The at least one photovoltaic cell may be arranged in an array. The planar first solar cover surface may include an optically transparent polymer layer.

[0124] A method for fabricating a solar panel is provided, comprising: at least one photovoltaic cell having a light-sensitive surface facing a planar surface of a transparent solar cover; and a corresponding radio frequency power module comprising a printed circuit board with radio frequency power circuitry in wired communication with the at least one photovoltaic cell for collecting power from the at least one photovoltaic cell, the radio frequency power circuitry being disposed on the planar surface of the PC board facing away from the transparent solar cover; extending a heat-deformable polymer sheet disposed on an opposite side of the at least one photovoltaic cell from the transparent solar cover across the surface area of ​​the transparent solar cover to form a laminate stack in the planar surface; transferring the laminate stack to a vacuum oven; and establishing a vacuum in the vacuum oven to remove air between layers of the laminate stack. heating the laminated stack to a deformation temperature of the heat-deformable polymer sheet; applying mechanical pressure to the stack perpendicular to the plane; restoring ambient air pressure in the vacuum oven to bond the heat-deformable polymer sheet onto the transparent solar cover; conformally pressing the heat-deformable polymer sheet onto the at least one photovoltaic cell and the radio frequency power module to form a packaged array of photovoltaic modules; and mounting the packaged array of photovoltaic modules in a frame.

[0125] The method may further include disposing a transparent thermally crosslinkable polymer sheet over the transparent solar cover prior to disposing the at least one photovoltaic cell and the radio frequency power module on the transparent solar cover.

[0126] Disposing the heat-deformable polymer sheet can include disposing a heat-deformable cross-linkable polymer sheet. Disposing the heat-deformable cross-linkable polymer sheet can include disposing a sheet including one or more layers of one or more of polyethylene terephthalate, biaxially oriented polyethylene terephthalate, ethylene vinyl acetate, fluorinated polyester, polyvinyl fluoride, polyvinylidene fluoride, polyethylene vinyl acetate, polyethylene naphthalate, ethylene tetrafluoroethylene, fluoroethylene vinyl ether, tetrafluoroethylene hexafluoropropylene vinylidene fluoride copolymer, polyamide, polypropylene, polyethylene, and polyvinylidene fluoride-short sugar palm fiber. [Brief explanation of the drawings]

[0127] Example embodiments are shown in the referenced figures of the drawings. In the drawings, which are not necessarily drawn to scale, numerals may describe like components in different views. Like numerals with different subscripts may represent different instances of like components. The drawings illustrate generally, by way of example, and not by way of limitation, various embodiments described herein. It is intended that the embodiments and drawings disclosed herein be considered illustrative and not limiting.

[0128] [Figure 1] 1 is a schematic diagram of a wireless power transfer system in accordance with an exemplary embodiment.

[0129] [Figure 2A] 2A, 2B, and 2C depict antennas that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements. [Figure 2B] 2A, 2B, and 2C depict antennas that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements. [Figure 2C]2A, 2B, and 2C depict antennas that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements.

[0130] [Figure 3A] 3A and 3B show side profile views of antennas that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements. [Figure 3B] 3A and 3B show side profile views of antennas that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements.

[0131] [Figure 4A] 4A, 4B, 4C, and 4D depict side profile views of exemplary resonators that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements. [Figure 4B] 4A, 4B, 4C, and 4D depict side profile views of exemplary resonators that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements. [Figure 4C] 4A, 4B, 4C, and 4D depict side profile views of exemplary resonators that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements. [Figure 4D] 4A, 4B, 4C, and 4D depict side profile views of exemplary resonators that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements.

[0132] [Figure 5] 1A-1C illustrate cross sections of exemplary resonators that may be used in various exemplary embodiments, or by themselves, or in combination with other disclosed elements.

[0133] [Figure 6] FIG. 1 is a schematic diagram of a primary side of a wireless power transfer system in accordance with an illustrative embodiment.

[0134] [Figure 7] FIG. 1 is a schematic diagram of a secondary side of a wireless power transfer system in accordance with an illustrative embodiment.

[0135] [Figure 8] FIG. 8 is a schematic diagram of an exemplary power amplifier that may be used in various exemplary embodiments, or by itself, or in combination with other disclosed elements.

[0136] [Figure 9] FIG. 1 is a schematic diagram of an example self-synchronous rectifier that may be used in various example embodiments, or by itself, or in combination with other disclosed elements.

[0137] [Figure 10] 7 shows a more detailed schematic diagram of a V / I tuner according to FIG. 6 used to adjust the power signal to the transmitter resonator, according to an example.

[0138] [Figure 11] FIG. 1 illustrates a flowchart of a near-field resonant wireless method for bimodally transferring power according to an adjustable transfer mode ratio at a resonant power signal oscillation frequency, according to an exemplary embodiment.

[0139] [Figure 12] FIG. 1 is a schematic diagram of a multi-transmitter near-field resonant wireless power transfer system for transferring power to a single receiver subsystem.

[0140] [Figure 13A] 13A and 13B show a multi-transmitter near-field resonant wireless power transfer system for transferring power to a single receiver subsystem. [Figure 13B]13A and 13B show a multi-transmitter near-field resonant wireless power transfer system for transferring power to a single receiver subsystem.

[0141] [Figure 14] FIG. 1 illustrates a multi-transmitter near-field resonant wireless power transfer system for transferring power to two or more receiver subsystems.

[0142] [Figure 15] FIG. 1 illustrates a flowchart of a wireless near-field method for transferring power from multiple transmitter subsystems to a single resonant receiver subsystem at variable resonant power signal oscillation frequencies.

[0143] [Figure 16] FIG. 10 shows a flowchart of another wireless near-field method for transferring power from multiple transmitter subsystems to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0144] [Figure 17] FIG. 1 illustrates a flowchart of a wireless near-field method for transferring power from multiple transmitter subsystems to two or more resonant receiver subsystems at variable resonant power signal oscillation frequencies.

[0145] [Figure 18] 10 shows a flowchart of another wireless near-field method for transferring power from multiple transmitter subsystems to two or more resonant receiver subsystems at variable resonant power signal oscillation frequencies.

[0146] [Figure 19A] FIG. 19A illustrates a near-field resonant wireless power transfer system for wirelessly transferring power from a photovoltaic solar cell to a power load.

[0147] [Figure 19B] FIG. 19B shows a power transfer system for transferring power from a photovoltaic solar cell to a power load.

[0148] [Figure 20A] 20A and 20B show front and back views of a solar cell array configured for use with the near-field resonant wireless power transfer system of FIG. 19A in a many-to-one configuration. [Figure 20B] 20A and 20B show front and back views of a solar cell array configured for use with the near-field resonant wireless power transfer system of FIG. 19A in a many-to-one configuration.

[0149] [Figure 21A] 21A and 21B show front and back views of a solar cell array configured for use with the near-field resonant wireless power transfer system of FIG. 19A in a one-to-one configuration. [Figure 21B] 21A and 21B show front and back views of a solar cell array configured for use with the near-field resonant wireless power transfer system of FIG. 19A in a one-to-one configuration.

[0150] [Figure 22A] 22A and 22B show front and back views of a solar array configured to use the near-field resonant wireless power transfer system of FIG. 19A in a row-based configuration. [Figure 22B] 22A and 22B show front and back views of a solar array configured to use the near-field resonant wireless power transfer system of FIG. 19A in a row-based configuration.

[0151] [Figure 23] FIG. 1 is a flowchart of a method for wirelessly transferring power from a photovoltaic solar cell to a power load.

[0152] [Figure 24] FIG. 10 is a flowchart of another method for wirelessly transferring power from a photovoltaic solar cell array to a power load.

[0153] [Figure 25] 10 shows a flowchart diagram of another method for wirelessly transferring power from a photovoltaic solar array to a power load.

[0154] [Figure 26] FIG. 10 is a flowchart of another method for wirelessly transferring power from a photovoltaic solar cell array to a power load.

[0155] [Figure 27A] FIG. 27A shows a diagram of a portion of an electric vehicle using an embodiment of a power transfer system.

[0156] [Figure 27B] FIG. 27B shows another view of a portion of an electric vehicle using an embodiment of the power transfer system.

[0157] [Figure 28A] FIG. 28A shows a drawing of a computer monitor using an embodiment of a power transfer system.

[0158] [Figure 28B] FIG. 28B shows a computer monitor using another embodiment of a power transfer system.

[0159] [Figure 29] 1 shows a flowchart of a method for transferring power from a DC power source to a power load.

[0160] [Figure 30] 1 shows a flowchart of a further method for transferring power from a DC power source to a power load.

[0161] [Figure 31] FIG. 1 shows a flowchart of a method for transferring power between transmit modules in a bimodal resonant near-field radio frequency power transfer system.

[0162] [Figure 32] 1 shows a schematic diagram of a bidirectional power transfer circuit device.

[0163] [Figure 33] 1 illustrates an implementation of a bidirectional power transfer circuit device.

[0164] [Figure 34A] FIG. 34A shows an implementation of a bidirectional power transfer circuit device mounted on the same silicon wafer as a photovoltaic cell.

[0165] [Figure 34B] FIG. 34B shows the coupled device of FIG. 34A with a resonator on the surface of a silicon wafer.

[0166] [Figure 35A] FIG. 35A illustrates a near-field resonant wireless power transfer system for wirelessly transferring power from a photovoltaic solar cell to an AC power load.

[0167] [Figure 35B] FIG. 35B shows a power transfer system for transferring power from a photovoltaic solar cell to an AC power load.

[0168] [Figure 36] FIG. 36 shows a schematic diagram of a bidirectional power transfer circuit device.

[0169] [Figure 37A] FIG. 37A shows a schematic diagram of a bidirectional power transfer system for transferring power between a DC power source and an AC power load using the frequency difference between two high frequency signals.

[0170] [Figure 37B] FIG. 37B shows a schematic diagram of a bidirectional power transfer system for transferring power between a DC power source and a variable power load, which can be AC ​​or DC, using the phase difference of two high frequency signals.

[0171] [Figure 37C]FIG. 37C shows a schematic diagram of a bidirectional power transfer system for transferring power between a DC power source and a variable power load, which can be AC ​​or DC, using a phase or frequency difference between two high frequency signals and multiple pairs of rectifier / amplifiers.

[0172] [Figure 37D] FIG. 37D shows a schematic diagram of a bidirectional power transfer system for transferring power between multiple DC power sources and variable power loads, which can be AC ​​or DC, using a phase or frequency difference between two high frequency signals and multiple HF switching signal generators and multiple pairs of rectifiers / amplifiers.

[0173] [Figure 38] FIG. 1 shows a rectified power signal in the form of a half-wave train and the results of the power signal evolution.

[0174] [Figure 39] FIG. 39 shows a flowchart of a method for transferring power between a DC power source, which may be AC ​​or DC, and a variable power load.

[0175] [Figure 40] 1 shows an exploded rear view of a photovoltaic module for wireless transmission of power comprising a photovoltaic cell and a radio frequency power module.

[0176] [Figure 41A] FIG. 41A shows a power transfer system for wireless or wired transfer of power from solar cells in a solar panel having multiple photovoltaic cells to a variable power load, which can be AC ​​or DC.

[0177] [Figure 41B] FIG. 41B shows a bimodal wireless power transfer system for transferring power from a photovoltaic cell in a solar panel having multiple photovoltaic cells to a variable power load, which can be AC ​​or DC.

[0178] [Figure 42A]FIG. 42A is a schematic exploded rear view of a solar panel for wireless or wired transmission of power based on an array of photovoltaic modules prior to conformal application of an encapsulation layer.

[0179] [Figure 42B] FIG. 42B is a schematic exploded rear view of a solar panel for bimodal wireless transmission based on an array of photovoltaic modules before conformal application of an encapsulation layer.

[0180] [Figure 43A] FIG. 43A shows a schematic side view of a photovoltaic module encapsulated under a conformal encapsulation layer.

[0181] [Figure 43B] FIG. 43B shows a schematic side view of a further implementation of a photovoltaic module encapsulated under a conformal encapsulation layer.

[0182] [Figure 44] FIG. 42C is a schematic exploded rear view of a solar panel for wireless transmission of power based on an array of photovoltaic modules including a protective cap prior to conformal application of an encapsulation layer, taking the system of FIG. 42B as an example.

[0183] [Figure 45] 1 shows a flow chart of a method for manufacturing a solar panel. DETAILED DESCRIPTION OF THE INVENTION

[0184] Corresponding reference characters indicate corresponding parts throughout the several views. While the drawings represent embodiments of the present invention, the drawings are not necessarily to scale and certain features may be exaggerated to better illustrate and explain the present invention. The flow charts are representative in nature, and actual embodiments of the present invention may include additional features or steps not shown in the drawings. The illustrations set forth herein illustrate embodiments of the present invention in one form, and such illustrations should not be construed as limiting the scope of the present invention in any way.

[0185] Throughout the following description, specific details are set forth to provide a more thorough understanding to those skilled in the art. However, well-known elements may not be shown or described in detail to avoid unnecessarily obscuring the present disclosure. Accordingly, the description and drawings are to be regarded in an illustrative rather than a restrictive sense.

[0186] One aspect of the present disclosure provides a wireless power transfer system including a transmitter (also referred to as a primary side) and a receiver (also referred to as a secondary side). Another aspect provides a wireless power transmitter that may be employed as part of other wireless power transfer systems. Another aspect provides a wireless power receiver that may be employed as part of other wireless power transfer systems. The transmitter according to some embodiments may include a resonator configured to transmit power by inductive power transfer and / or by capacitive power transfer. Similarly, the receiver according to some embodiments may include a resonator configured to receive power by inductive power transfer and / or by capacitive power transfer.

[0187] 1 is a simplified schematic diagram of a wireless power transfer (WPT) system 10 comprising a primary side 12, sometimes referred to as a transmitter, and a secondary side 14, sometimes referred to as a receiver. The primary side 12 comprises a transmitter module 20 and a transmitter resonator 30, and the secondary side 14 comprises a receiver module 40 and a receiver resonator 50.

[0188] The transmitter module 20 receives power as an input, including, for example, direct current (DC) power. Although not shown, the transmitter module 20 may include, for example, an inverter, a transmitter compensation network, and / or other components, as described further herein. The transmitter module 20 outputs power, including, for example, alternating current (AC) power, to the transmitter resonator 30.

[0189] The transmitter resonator 30 receives power as an input from the transmitter module 20 and may output a magnetic field 31A (e.g., a time-varying magnetic field) and / or an electric field 3IB (e.g., a time-varying electric field). In some embodiments, the transmitter resonator 30 outputs the magnetic field 31A for purposes of IPT. In some embodiments, the transmitter resonator 30 outputs the electric field 3IB for purposes of CPT. In some embodiments, the resonator 30 simultaneously outputs the magnetic field 31A and the electric field 3IB for purposes of simultaneous transfer of power through CPT and IPT. In some embodiments, the resonator 30 can switch between outputting the electric field 3IB for purposes of CPT, outputting the magnetic field 31A for purposes of IPT, and simultaneously outputting the magnetic field 31A and the electric field 3IB for purposes of simultaneous transfer of power through CPT and IPT.

[0190] The adjective term "bimodal" is used herein to describe a system configured for simultaneous capacitive and inductive signaling.

[0191] In the presence of a magnetic field 31A, a current may be induced in the receiver resonator 50 for purposes of IPT. In the presence of an electric field 3IB, an alternating potential may be induced on the receiver resonator 50 (or its antenna(s)).

[0192] When a current is induced in the receiver resonator 50 by the magnetic field 31A, such current can be output to the receiver module 40; similarly, when an alternating potential is induced on the receiver resonator 50 by the electric field 3IB, a current can be flowed by the receiver resonator 50 into the receiver module 40.

[0193] The receiver module 40 may receive power (e.g., AC power) from the receiver resonator 50 as an input and may output power (e.g., DC power) to a load. The load may be an electrical charge for a power storage device such as a battery or a supercapacitor. As a non-limiting example, the load may comprise or be an element of an electric bicycle (also called an e-bicycle or e-bike), such as an e-bicycle that is part of a bike-sharing fleet, an automobile, a boat, etc. Although not shown, the receiver module 40 may comprise, for example, a rectifier, a receiver compensation network, and / or other components as further described herein.

[0194] The WPT system 10 may be configured to adjust the ratio of power transferred from the transmitter module 20 via CPT to the receiver module 40 via IPT for various reasons. For example, the transfer mode ratio may be adjusted to increase the proportion of power delivered by CPT when the distance between the transmitter resonator 30 and the receiver resonator 50 increases, increasing the proportion of power delivered by IPT when a living organism is in close proximity to the WPT system 10, increasing the proportion of power delivered by CPT when an object (e.g., a metal object) is in close proximity to the WPT system 10, increasing the proportion of power delivered by CPT when the alignment between the transmitter resonator 30 and the receiver resonator 50 deteriorates, and / or any combination of the above.

[0195] In some embodiments, the transfer mode ratio may be adjusted according to a maximum power point tracking technique, such as, but not limited to, those sometimes used in wind turbines and solar panels (e.g., S. DehghAni, S. AbbAsiAn, and T. Johnson, "Adjustable LoAd With tracking Loop to Be Variable RF Input Power Condition," IEEE TransAnsActions on Microwave Theory and Techniques, vol. 64, no. 2, pp. 343-352, February 2016). In some embodiments, the transfer mode ratio may be adjusted according to a machine learning algorithm. For example, in some embodiments, if the WPT system 10 determines that the WPT efficiency is undesirably low, the WPT system 10 may increase the proportion of power delivered by CPT (or IPT). If the WPT efficiency is adversely affected by increasing the reliance on CPT (or IPT), the WPT system 10 may decrease the reliance on CPT (or IPT). This process can be repeated iteratively until the desired / maximum WPT efficiency is achieved.

[0196] Each of the transmitter resonator 30 and receiver resonator 50 may include multiple antennas 80 arranged in various configurations.

[0197] Antenna 80 may comprise any suitable antenna having high self-inductance and high self-capacitance capable of generating both magnetic field 31A and electric field 3IB (separately and / or simultaneously) for CPT and IPT purposes. Figures 2A, 2B, and 2C show non-limiting examples of antennas 80, 180, 280, which, for purposes herein, have a self-inductance large enough to enable the antenna to generate a magnetic field suitable for IPT purposes. Similarly, high self-capacitance here is a self-capacitance large enough to enable the antenna to generate an electric field suitable for CPT purposes.

[0198] FIG. 2A illustrates an antenna 80 according to some embodiments. The antenna 80 may comprise any suitable conductive material. For example, the antenna 80 may comprise copper, gold, silver, aluminum, other suitable materials, or combinations thereof. As can be seen in FIG. 2A , the antenna 80 comprises an elongated element 80A having a rectangular (e.g., square) cross-section that is bent or formed into the shape of a generally planar rectangular (in the XY plane) coil such that adjacent wrappings of the elongated element 80A are separated by a gap 80B. While the gap 80B is depicted as being generally constant along the length of the elongated element 80, this is not required.

[0199] The size of gap 80B may be reduced to increase the self-inductance of antenna 80. To increase the self-capacitance of antenna 80, the number of bends (e.g., bends 82A) of elongated element 80A may be increased, the number of corners and edges (e.g., edges 82B) of elongated element 80A may be increased, the length of elongated element 80A may be increased, and / or the thickness 80C of elongated element 80A may be increased.

[0200] 2B shows another non-limiting example of an antenna 180 according to some embodiments. The antenna 180 is substantially similar to the first antenna 80, except that instead of being bent or formed into the shape of a generally planar rectangular coil, the elongated elements 180A are bent or formed into the shape of a generally planar zigzag with square corners, as shown in FIG. 2B. Like the antenna 80, adjacent zigs or zags of the elongated elements 180A are spaced apart by a gap 180B. While the gap 180B is depicted as being generally constant along the length of the elongated elements 180, this is not required.

[0201] The size of gap 180B can be reduced to increase the self-inductance of antenna 180. To increase the self-capacitance of antenna 180, the number of bends (e.g., bend 182A) of elongated element 180A can be increased, the number of corners and edges (e.g., edge 182B) of elongated element 180A can be increased, and / or the thickness 180C of elongated element 180A can be increased.

[0202] 2C shows another non-limiting example of an antenna 280 according to some embodiments. The antenna 280 is substantially similar to the first antenna 80, except that instead of being bent or formed into the shape of a generally planar rectangular coil, the elongated element 280A is bent or formed into a generally planar circular shape (in the XY plane) having a hub element 280A from which sector elements 280C extend radially outward. Adjacent sector elements 280C are spaced apart from one another by gaps 280B.

[0203] The size of gap 280B may be reduced to increase the self-inductance of antenna 280. To increase the self-capacitance of antenna 280, the number of sectors 280C may be increased, the number of corners and edges (e.g., edges 28A) of hub 280A and / or sectors 280C may be increased, and / or the thickness 280C of elongated hub 280A and / or sectors 280C may be increased.

[0204] 2A, 2B, and 2C show exemplary, non-limiting embodiments of antennas 80, 180, 280, it should be understood that many other shapes and configurations of suitable antennas 80 may be employed in the resonators described herein. Non-limiting examples of modifications that may be made to the illustrated antennas include changing the cross-sectional shape of the elongated elements 80A, 180A to something other than rectangular (e.g., triangular, circular, hexagonal, etc.), changing the 90° bends 82A, 182A to non-90° or rounded, and changing the XY plane shape of the first transmitter antenna 80 to something other than rectangular or circular using non-repeating patterns such as bends and corners.

[0205] Although the antennas 80, 180, 280 are described and illustrated herein as being relatively flat or planar (e.g., having substantially no thickness variation in the Z direction), this is not required. In some embodiments, the antennas 80, 180, 280 may have a conical concave or conical convex shape, as shown in FIGS. 3A and 3B . For example, the antennas herein may have a conical spiral shape (not shown). In some embodiments, the antenna 80 may have a rectangular conical spiral shape such that the inner winding of the antenna 80 is spaced apart in the Z direction from the outer winding of the antenna 80; such a conical shape may allow the resonator to be used for a wider range of resonant frequencies. In other embodiments, the Z-direction thickness of the first transmitter antenna may vary in other ways.

[0206] The antennas 80, 180, 280 can be arranged in a configuration similar to the plate configuration in a CPT WPT system, for example. For example, in some embodiments, in a two-antenna WPT system, the transmitter resonator 30 may include a first transmitter antenna 32 arranged parallel to a first receiver antenna 52 of the receiver resonator 50, as shown in FIG. 4A for CPT purposes, where the mutual capacitance between the two antennas 32, 52 provides a path for current to flow forward to the receiver side, and a conductive path (e.g., ground) allows current to flow backward to the transmitter side. For IPT purposes, driving a current through the first transmitter antenna 32 generates a magnetic field 31A that can induce a current in the first receiver antenna 52, which can generate a potential difference between the first transmitter antenna 32 and the first receiver antenna 52, thereby generating an electric field 3IB.

[0207] First transmitter antenna 32 may comprise any suitable antenna having high self-filling and high self-capacitance that is capable of generating both magnetic field 31A and electric field 3IB (separately and / or simultaneously). For example, first transmitter antenna 32 may comprise one of antennas 80, 180, 280, or any other antenna described herein.

[0208] The first receiver antenna 52 may comprise any suitable antenna having high self-filling and high self-capacitance that can have currents induced therein by the magnetic field 31A and (separately and / or simultaneously) have a potential difference thereon due to the electric field 3IB. In some embodiments, the first receiver antenna 52 may be substantially similar to the first transmitter antenna 32 (e.g., the first receiver antenna 52 may have the same or otherwise the same characteristics of any of the antennas described or depicted herein). In some embodiments, the antennas 32, 52 may be different from one another (e.g., the first transmitter antenna 32 may comprise antenna 80, while the first receiver antenna 52 may comprise antenna 180).

[0209] In some embodiments, to improve coupling between the first transmitter antenna 32 and the first receiver antenna 52, the XY plane area of ​​the first transmitter antenna 32 is smaller than the XY plane area of ​​the first receiver antenna 52.

[0210] 4B shows another example configuration of antennas 80, 180, 280, and in some embodiments, FIG. 4B shows a four-antenna stack (or four-antenna vertical) WPT system. Transmitter resonator 130 and receiver resonator 150 each include two antennas. Together, one antenna of transmitter resonator 30 and one antenna of receiver resonator 150 provide a forward path for power, and the other antenna of transmitter resonator 130 and the other antenna of receiver resonator 150 provide a return path for power.

[0211] For purposes of IPT, a magnetic field is generated that can induce currents in the first and second receiver antennas 152, 154 by driving current through the transmitter antennas 132, 134, and for purposes of CPT, a potential difference can be applied between the first antenna 132 and the second antenna 134 to induce a potential across the first and second receiver antennas 152, 154.

[0212] As shown in FIG. 4B, the transmitter resonator 130 comprises a first transmitter antenna 132 and a second transmitter antenna 134 separated in the Z direction by a spacer 138 .

[0213] The first transmitter antenna 132 may comprise any suitable antenna having high self-inductance and high self-capacitance that is capable of generating both the magnetic field 31A and the electric field 3IB (separately and / or simultaneously). For example, the first transmitter antenna may comprise one of antennas 80, 180, 280, or any other antenna described herein.

[0214] The spacer 138 may include any suitable material. For example, the spacer 138 may include air, a dielectric material, a ferrite, or some combination thereof. The spacer 138 may have a permittivity selected to vary the electric field 31A and / or a magnetic permeability selected to vary the magnetic field 3IB. The spacer 138 may include a high permittivity material to increase the capacitance of the transmitter resonator 130, and the thickness and planar area of ​​the spacer 138 may depend on the thickness and / or planar area of ​​the first and second transmitter antennas 132, 134.

[0215] The second transmitter antenna 134 may comprise any suitable antenna having high self-inductance and high self-capacitance capable of generating both the magnetic field 31A and the electric field 3IB (separately and / or simultaneously). In some embodiments, the second transmitter antenna 134 may be substantially similar to the first transmitter antenna 132 (e.g., the second transmitter antenna 134 may have the same or otherwise the same characteristics of any of the antennas described or depicted herein). In some embodiments, the first and second transmitter antennas 132, 134 and the first and second receiver antennas 152, 154 may be different from one another (e.g., the first and second transmitter antennas 132, 134 may be similar to antenna 80, while the first and second receiver antennas 152, 154 may be similar to antenna 180).

[0216] In some embodiments, the XY plane area of ​​the second transmitter antenna 134 may be a different size than the XY plane area of ​​the first transmitter antenna 132. In some embodiments, to ensure coupling between each pair of antennas, the XY plane area of ​​the second transmitter antenna 134 is smaller than the XY plane area of ​​the first transmitter antenna 132. In some embodiments, the XY plane area of ​​the second transmitter antenna 134 may be larger than the XY plane area of ​​the first transmitter antenna 132.

[0217] In some embodiments, the second transmitter antenna 134 is substantially complementary in size and / or shape to the first antenna 132 such that the first transmitter antenna 132 does not substantially overlap in the Z direction with the second transmitter antenna 134. Figure 5 shows a schematic diagram of an XZ plane cross section of a portion of the transmitter resonator 130, with the first transmitter antenna 132 and the second transmitter antenna 134 each shaped similarly to the first transmitter antenna 180 of Figure 2B. As can be seen, the portions 132A-1, 132A-2, and 132A-3 of the elongated element 132A of the first transmitter antenna 132 overlap in the Z direction with the gaps 134B-1, 134B-2, and 134B-3 of the second transmitter antenna 134 (e.g., a line oriented in the Z direction passing through the portion 132A-1 of the elongated element 132A of the first antenna 132) overlap in the Z direction with the gaps 132B-1, 132B-2, and 132B-3 of the first transmitter antenna 132 (e.g., a line oriented in the Z direction passing through the portion 134A-1 of the elongated element 134A of the second antenna 134 passes through the gap 132B-1 of the second antenna 134). The complementary shapes of the first transmitter antenna 132 and the second antenna 134 can reduce parasitic energy losses experienced by the transmitter resonator 130, and in some embodiments, the first and second transmitter antennas 132, 134 may not be perfectly complementary, but may have one or more complementary portions.

[0218] The receiver resonator 150 comprises a first receiver antenna 152 and a second receiver antenna 154 separated in the Z direction by a spacer 158, where the first receiver antenna 152 may be substantially similar to any of the antennas 80, 180, 280 or as otherwise described herein. The second receiver antenna 154 may also be substantially similar to any of the antennas 80, 180, 280 or as otherwise described herein. Like the first and second transmitter antennas 132, 134, the first and second receiver antennas 152, 154 may be complementary (or partially complementary) in size and / or shape.

[0219] In some embodiments, to adjust the self-inductance or self-capacitance of the receiver resonator 150, the XY plane areas of the first and second receiver antennas 152, 154 are different from the XY plane areas of the first and second transmitter antennas, as shown in FIG. 4B. For example, in some embodiments, the XY plane areas of the first and second receiver antennas 152, 154 are larger than the XY plane areas of the first and second transmitter antennas 132, 134, as shown in FIG. 2A. Such an XY plane area difference may improve the ability of the receiver resonator 150 to capture more of the magnetic field 31A and / or the electric field 3IB.

[0220] Spacer 158 may include any suitable spacer. Spacer 158 may include the same or similar material as spacer 138, and compared to spacer 158, spacer 138 may have a smaller Z-direction dimension to achieve a desired self-capacitance and / or self-inductance. This may effectively change the coupling coefficient of the link between primary 12 and secondary 14 and the impedance of primary 12, and different compensation networks may be used on both primary 12 and secondary 14 to accommodate such coupling coefficient and impedance changes.

[0221] Compared to the four-antenna parallel structure shown in Figure 4C, the stacked configuration in Figure 4B is much more compact in the XY plane. Additionally, because all antennas can be centered, this configuration is robust to angular misalignment. Specifically, if the antennas are circular, angular rotation does not affect the coupling capacitance. However, compared to the four-antenna parallel structure shown in Figure 4C, the transconductance of the stacked configuration in Figure 4B may be lower due to increased cross-coupling capacitance.

[0222] 4C shows another example configuration of antennas 80, 180, 280, and in some embodiments, FIG. 4C shows a four-antenna parallel (or four-antenna horizontal) WPT system. Transmitter resonator 230 and receiver resonator 250 each include two antennas. One antenna of transmitter resonator 230 and one antenna of receiver resonator 250 together provide a forward path for power, and the other antenna of transmitter resonator 230 and the other antenna of receiver resonator 250 provide a return path for power.

[0223] For purposes of IPT, by driving current through the transmitter antennas 232, 234, a magnetic field is generated that can induce currents in the first receiver antenna 252 and the second receiver antenna 254, and for purposes of CPT, a potential difference can be generated between the first antenna 232 and the second antenna 234 to generate an electric field 3IB for inducing a potential across the first receiver antenna 252 and the second receiver antenna 254.

[0224] Compared to the transmitter resonator 130 and receiver resonator 150 shown in FIG. 4B, the transmitter resonator 230 and receiver resonator 250 having a horizontal arrangement of the antennas may be desirable in applications where there are limitations on the Z-direction dimensions of the resonators.

[0225] The transmitter resonator 230 includes a first transmitter antenna 232 and a second transmitter antenna 234 separated in the X direction by a spacer 238, and separating the first and second transmitter antennas 232, 234 in the X direction may reduce parasitic energy losses. The first and second transmitter antennas 232, 234 may be substantially similar to the first and second transmitter antennas 132, 134, the spacer 238 may be substantially similar to the transmitter resonator 130, and the first transmitter antenna 232 may have an XY plane area larger than the XY plane area of ​​the second transmitter antenna 234 to improve the forward path for power transfer.

[0226] The spacer 238 may comprise any suitable material. For example, the spacer 238 may comprise air, a dielectric material, a ferrite, or a combination thereof. The spacer 238 may have a permittivity selected to alter the electric field 31A and / or a magnetic permeability selected to alter the magnetic field 3IB. The spacer 238 may comprise a high permittivity material to increase the capacitance of the transmitter resonator 230, and the thickness and planar area of ​​the spacer 238 may depend on the thickness and / or planar area of ​​the first and second transmitter antennas 232, 234; in some embodiments, electrical isolation may be desirable and a low permittivity material may be employed for the spacer 238 (e.g., for shielding).

[0227] The receiver resonator 250 includes a first receiver antenna 252 and a second receiver antenna 254 separated in the X direction by a spacer 258. Separating the first and second receiver antennas 252, 254 in the X direction can reduce parasitic energy losses. The first and second receiver antennas 252, 254 can be substantially similar to the first and second receiver antennas 152, 154, the spacer 258 can be substantially similar to the receiver resonator 150, and the first receiver antenna 252 can have an XY plane area greater than the XY plane area of ​​the second receiver antenna spacer 258.

[0228] Spacer 258 may comprise the same or similar material as spacer 238, and compared to spacer 258, spacer 238 may have a smaller Z-direction dimension to achieve a desired self-capacitance and / or self-inductance. This may effectively change the coupling coefficient of the link between primary 12 and secondary 14 and the impedance of primary 12, and different compensation networks may be used on both primary 12 and secondary 14 to accommodate such coupling coefficient and impedance changes.

[0229] In some embodiments, the XY planar area of ​​spacer 258 may be different from the XY planar area of ​​spacer 238 to change the self-inductance or self-capacitance of transmitter resonator 230 or receiver resonator 250; for example, compared to spacer 258, spacer 238 may have a smaller XY planar area, as shown.

[0230] Figure 4D shows another example configuration of antennas 80, 180, and 280. In some embodiments, Figure 4D shows a six-antenna WPT system that combines the stacked configuration of Figure 4B and the parallel configuration of Figure 4C. Each of the transmitter resonator 130 and receiver resonator 150 includes three antennas. One of the first and second transmitter antennas 332, 334 and one of the first and second receiver antennas 352, 354 provides a forward path for power, and the other of the first and second transmitter antennas 332, 334 and the other of the first and second receiver antennas 352, 354 provides a return path for power. The third transmitter antenna 336 and receiver antenna 356 serve as an auxiliary antenna to increase the equivalent self-capacitance and as an electric field shield. In some embodiments, the third transmitter antenna 336 and the receiver antenna 356 are passive (e.g., no potential difference is applied between the third transmitter antenna 336 and the receiver antenna 356 and / or no current is driven through the third transmitter antenna 336 and the receiver antenna 356). For purposes of IPT, driving current through one or more of the transmitter antennas 332, 334, 336 generates a magnetic field that may induce current in the first receiver antenna 352, 354, 356, and for purposes of CPT, may generate a potential difference between any of the first transmitter antenna 332, the second transmitter antenna 334, and / or the third transmitter antenna 336, thereby generating an electric field 3IB.

[0231] The transmit resonator 330 comprises a first transmit antenna 332 and a second transmit antenna 334 separated in the X direction by a spacer 338, and a third transmit antenna 336 separated from the first and second transmit antennas and the spacer 338 by a second spacer 339. The third transmitter antenna 336 can provide electric field shielding to reduce unwanted escape of magnetic fields from the transmit resonator 330, and by modifying the spacer 339, electric or magnetic field shielding or shaping may also be possible.

[0232] The first, second, and third transmit antennas 332, 334, 336 may be substantially similar to either of the first and second transmitter antennas 132, 134, the spacers 338, 339 may be substantially similar to the transmit resonator 130, the first transmitter antenna 332 may have a larger XY plane area than that of the second transmitter antenna 334, and the third transmitter antenna 336 may have a larger XY plane area than either of the first and second transmitter antennas 334, 332.

[0233] The spacers 338, 339 may comprise any suitable material. For example, the spacers 338, 339 may comprise air, a dielectric material, a ferrite, or a combination thereof. The spacers 338, 339 may have a permittivity selected to alter the electric field 31A and / or a magnetic permeability selected to alter the magnetic field 3IB. The spacers 338, 339 may comprise a high permittivity material to increase the capacitance of the transmitter resonator 230, and the thickness and planar area of ​​the spacers 338, 339 may depend on the thickness and / or planar area of ​​the first, second, and third transmitter antennas 332, 334, 336. In some embodiments, electrical isolation may be desirable and a low permittivity material may be used for the spacers 338, 339 (e.g., for shielding).

[0234] The receiver resonator 350 includes a first receiver antenna 352 and a second receiver antenna 354 separated in the X direction by a spacer 358, and a third receiver antenna 356 separated from the first and second receiver antennas and the spacer 358 by a second spacer 359. The third receiver antenna 356 may provide electric field shielding to reduce undesired escape of electric fields from the receiver resonator 350, and the third receiver antenna 356 may include a ferrite sheet or surface to provide magnetic field shielding to reduce undesired escape of magnetic fields from the transmitter. The first, second, and third receiver antennas 352, 354, 356 may be substantially similar to either of the first and second receiver antennas 152, 154. The spacers 358, 359 may be substantially similar to either of the first and second receiver antennas 152, 154. Similar to the receiver resonator 150, the first receiver antenna 352 is separated from the second receiver antenna 354. The third receiver antenna 356 may have a larger XY plane area than either of the first and second receiver antennas 354, 352.

[0235] Spacers 358, 359 may comprise any suitable spacers. Spacers 358, 359 may comprise the same or similar material as spacers 338, 339, or a different material than spacers 338, 339, and compared to spacers 358, 359, spacers 338, 339 may have a smaller Z-direction dimension to achieve a desired self-capacitance and / or self-inductance. This can effectively change the coupling coefficient of the link between primary 12 and secondary 14 and the impedance of primary 12, and different compensation networks can be used on both primary 12 and secondary 14 to accommodate such coupling coefficient and impedance changes.

[0236] In some embodiments, the XY-plane area of ​​spacer 358 may be different from the XY-plane area of ​​spacer 338 to change the self-inductance or self-capacitance of transmitter resonator 330 or receiver resonator 350; e.g., spacer 338 may have a smaller X-direction dimension compared to spacer 358. In some embodiments, the Z-direction dimension of spacer 359 may be different from the Z-direction dimension of spacer 339 to change the self-inductance or self-capacitance of transmitter resonator 330 or receiver resonator 350; e.g., spacer 339 may have a smaller Z-direction dimension compared to spacer 359. This may effectively change the coupling coefficient of the link between primary side 12 and secondary side 14 and the impedance of primary side 12; different compensation networks may be used on both primary side 12 and secondary side 14 to accommodate such coupling coefficient and impedance changes.

[0237] In some embodiments, a magnetic shield may be provided around one or more of the transmitter resonator 30 and the receiver resonator 50; for example, ferrite may be used as a magnetic shield and to reduce undesirable eddy currents in nearby metal objects. Ferrite (or another suitable material) may also be used to isolate the transmitter resonator 30 and the receiver resonator 50 from surrounding metal objects, and thus may serve to increase the self-inductance of the antenna and / or the mutual inductance of the resonators.

[0238] 6 shows a schematic diagram of the primary side 12 including the transmitter module 20 and the transmitter resonator 30, according to some embodiments. The transmitter resonator 30 may comprise any of the transmitter resonators 30, 130, 230, 330, or may be otherwise described herein.

[0239] The transmitter module 20 includes a controller 22 configured to receive various inputs from sensors 24 (e.g., a load detector 24A, a transmitter power sensor 24B, an ambient object detector 24C, and / or a distance detector 24D) and to output control signals to various components 26 (e.g., an oscillator 26A, a power amplifier 26B, a filter network 26C, a matching network 26D, a compensation network 26E, and a V / I tuner 26F).

[0240] Load detector 24A is configured to detect the presence of a load 70 (shown in FIG. 7 ) connected to secondary side 14. Load 70 may be, for example, a battery of an electric vehicle such as an e-bike or electric car, or any other suitable item requiring a power input. Load detector 24A may be implemented using physical sensors (e.g., without limitation, a light sensor, a pressure sensor, an infrared sensor, or a proximity sensor) and appropriate software or firmware. For example, in some embodiments, power (e.g., current and voltage) is measured at point 24E to determine the power being drawn by transmitter resonator 30 (e.g., as measured by transmitter power sensor 24B). If the amount of power being drawn by transmitter resonator 30 increases above a baseline, load detector 24A can signal to controller 22 that load 70 is present.

[0241] In other embodiments, the load detector 24A may be configured to measure the input impedance of the transmitter resonator 30 as seen by the transmitter module 20 at point 24E. The presence of a coexisting receiver in proximity to the transmitter resonator 30, including a secondary 14 configured to drive a load 70, changes the input impedance of the transmitter resonator 30. This impedance change, provided to the controller 22 by the load detector 24A, may be used by the transmitter controller 22 to determine whether a coexisting receiver is present in proximity to the transmitter resonator 30. , the impedance changes induced in the transmitter resonator 30 by different receivers are so distinct that the controller 22 is not only able to detect the presence or absence of a receiver in proximity to the transmitter resonator 30 but also to distinguish between different types of receivers, for example, but not limited to, different models of mobile phones or digital tablets.

[0242] The transmitter power sensor 24B can measure the power (e.g., measure the current and voltage) at point 24E to determine how much power is being drawn by the transmitter resonator 30, and such information can be used, for example, by the load detector 24A, or can be used to determine whether there is desirably efficient coupling between the transmitter resonator 30 and the receiver resonator 50.

[0243] The ambient object detector (SOD) 24C is configured to determine whether an object (e.g., a living object such as a human or animal, or an inanimate object such as a metal piece) is in proximity to the transmitter resonator 30. The SOD 24C may be implemented using a physical sensor (e.g., without limitation, an optical sensor, a pressure sensor, an infrared sensor, a proximity sensor, a RADAR, or a LIDAR). This can be done by or with appropriate software or firmware. For example, if the power drawn by the transmitter resonator 30 (as measured by the transmitter power sensor 24B) drops during IPT, the SOD's software may determine that a metal piece (or any conductive object) is in proximity to the transmitter resonator 30 or the receiver resonator 50, and the SOD may provide a signal to the controller 22 indicating such presence. In some embodiments, the controller 22 can increase the rate of power delivered by the CPT when a metal object is detected in proximity to the transmitter resonator 30 or the receiver resonator 50, and the controller 22 can be configured to increase the power supply to the transmitting resonator 30 in the absence of a living organism being detected by the SOD 24C (e.g., above an adjusted level in the presence of a living organism), or in the proximity of a living organism being detected by the SOD 24C, the controller 22 can be configured to decrease the power supply to the transmitter resonator 30 below an adjusted level.

[0244] Distance detector 24D is configured to determine the distance between transmitter resonator 30 and receiver resonator 50. Distance detector 24D may be equipped with a physical sensor (such as, without limitation, an optical sensor, an ultrasonic sensor, an infrared sensor, a proximity sensor, a RADAR, or a LIDAR) and appropriate software or firmware. For example, distance detector 24D may be configured to determine the distance between transmitter resonator 30 and receiver resonator 50 based on changes in transmit power measured by transmit power sensor 24B.

[0245] In one embodiment, one or more temperature sensors may monitor the temperature in the transmit resonator 30 or the receiver resonator 50, and if the temperature exceeds a predetermined limit, the controller 22 may cause the transmit module 20 to reduce the rate of power delivered by the IPT, reduce the overall power supply to the transmit resonator 30, or cut off the power supply to the transmit resonator 30 to prevent a fire hazard or thermal runaway.

[0246] The oscillator 26A may be configured to control the frequency band, and / or bandwidth, and / or duty cycle (phase) (e.g., 5% to 50%) of the current being delivered to the transmit resonator 30 in response to a signal from the controller 22.

[0247] Power amplifier 26B may be used to convert DC power to AC power. Power amplifier 26B may be used to adjust the power supplied to transmitter resonator 30 in response to a signal from controller 22, and in some embodiments, controller 22 may send a signal to power amplifier 26B to adjust the reflection coefficient of power amplifier 26B. In some embodiments, controller 22 may send a signal to power amplifier 26B to turn off (or sleep) when load detector 24A does not detect a load or to turn on when load detector 24A detects a load.

[0248] Power amplifier 26B may comprise a switch-mode power amplifier (single-ended mode or differential configuration) that may be configured to receive a square (sine) wave from oscillator 26A and generate a sine wave of a particular frequency desired to drive transmit resonator 30; FIG. 8 is a schematic diagram of an exemplary power amplifier 26B that may be used in transmitter 30, where power amplifier 26B may be a differential switch-mode amplifier. Power amplifier 26B has three inputs: two input signals that drive active devices (transistors) 127C, 127D, and a DC voltage at source 127E that is used to control the output power and operating region of the active device.

[0249] Different load terminations are used to improve performance (e.g., output power, power conversion efficiency) and reduce unwanted harmonic levels. In some embodiments, a third harmonic termination 127F is placed in series with a shunt to shape the voltage waveform at the drain node 127G. A second harmonic termination 124H is placed in parallel. The drain node 127G is branched to shape the voltage waveform at the drain node 127G. A first harmonic termination 1271 is arranged in series with the drain node 127G to shape the voltage waveform. The effect of the third harmonic termination may be considered in the second and first harmonic terminations 124H and 1271, and the effect of the second harmonic termination may be considered in the first harmonic termination 1271. In the differential configuration of the power amplifier 26B, the AC load 128J (which receives the output power) is arranged in series. The charging rate of the AC load 127J may be a function of the transmitter resonator 30, the receiver resonator 50, and / or their alignment and position. The power amplifier 26B may be configured to generate sufficient power in the transmitter resonator 30 so that an E field or an H field, or any combination of E and H fields, can be generated by the transmitter resonator 30 and captured by the receiver resonator 50.

[0250] Amplifier 26B may include two phase shifters 125L in a differential configuration (but only one phase shifter in a single-ended configuration). Phase shifter 127L adjusts the appropriate phase difference between AC signal overload 127J and the gate signals of transistors 127C and 127D. The phase difference between the gate signals and AC signal overload 127J can change the power amplification performance, such as the power conversion efficiency and operating range of the transistors. It can also change the output impedance of transistors 127C and 127D and / or the optimal AC load 128J of power amplifier 26B.

[0251] Amplifier 26B may include two level shifters 128K in a differential configuration (but only one level shifter in a single-ended configuration). Level shifter 127K may adjust the appropriate amplitude for the gate signals of transistors 127C and 127D. The amplitude level of the gate signals may change the amplification performance (e.g., the power conversion efficiency and operating region of the transistors).

[0252] Amplifier 26B may be reconfigurable to function as a rectifier, in some embodiments, as a self-synchronous rectifier. As part of such reconfiguration, integrated phase shifter 127L and integrated level shifter 128K (see FIG. 8) may be adjusted to enable amplifier 26B to function as rectifier 26B based on the inherent amplification and switching functions of transistors 127C and 127D. This reconfigurability of amplifier 26B between operation as an amplifier and as a rectifier allows transmitter module 20 to be controllably reconfigured between transmitter mode and receiver mode, respectively. Reconfiguration may occur under instructions from controller 22; when amplifier 26B is reconfigured from an amplifier to a rectifier, AC load 127J changes to AC source 127J, and when amplifier 26B is reconfigured from an amplifier to a rectifier, DC source 127E is reconfigured to a DC load. Application of transmitter module 20 in receiver mode is addressed below after describing secondary side 14 and its receiver module, as shown in more detail in FIG. 7.

[0253] The filter network 26C can adjust the frequency response, such as bandwidth, cutoff frequency, 3 dB frequency, gain, etc., provided to the transmitter resonator 30 in response to signals from the controller 22, and the filter network 26C can be configured to adjust the shape of the waveform of the power within the transmitter module 20 to increase the efficiency of the transmitter module 20.

[0254] Matching network 26D may be configured to adjust the impedance to match the output of power amplifier 26B to transmitter resonator 30.

[0255] The compensation network 26E may be provided to drive the transmitter resonator 30 at a desired resonant frequency (e.g., the resonant frequency of the receiver resonator), thereby increasing the mutual magnetic flux, reducing heat generation, and improving power transfer efficiency. The compensation network 26E may include one or more capacitors to increase capacitance and one or more inductors to increase inductance. The compensation network 26E may be configured to increase capacitance (and / or decrease inductance) and increase inductance (and / or decrease capacitance) as desired. When the transfer mode ratio is 100% CPT, the compensation network 26E may function similarly to any known CPT compensation network (e.g., the compensation network 26E may function to increase inductance). Similarly, when the transfer mode ratio is 100% IPT, the compensation network 26E may function similarly to any known IPT compensation network (e.g., the compensation network 26E may function to increase capacitance). However, when the transfer mode is partial CPT and partial IPT, the capacitance of the transmitter resonator 30 naturally provides compensation for the inductance of the transmitter resonator 30, and the inductance of the transmitter resonator 30 naturally compensates for the capacitance of the transmitter resonator 30, so less compensation may be required; for example, at approximately 50% IPT and 50% CPT (e.g., a transfer mode ratio equal to 1), the compensation network may be substantially limited, thereby increasing the efficiency of the WPT system 10.

[0256] As another example, between approximately 40-60% IPT and 40-60% CPT, the compensation network may not be required at all or in use, thereby increasing the efficiency of the WPT system 10. To this end, the compensation network 26E may include fewer or smaller inductors and / or capacitors compared to CPT WPT systems and / or pure IPT WPT systems that require significant compensation. In some embodiments, if the capacitance of the transmitter resonator 30 is sufficiently low, additional compensation may be provided by the compensation network 26E. Similarly, if the inductance of the transmitter resonator 30 is sufficiently low, additional compensation may be provided via the compensation network 26E. The controller 22 may signal how many types of compensation are needed to the compensation network 26E based on, for example, the transfer mode ratio, the distance between the transmitter resonator 30 and the receiver resonator 50, the amount of power drawn by the transmitter resonator 30, power transfer efficiency, etc.

[0257] In some embodiments, the magnitude of compensation by compensation network 26E (e.g., an increase in capacitance or an increase in inductance) is proportional to the absolute value of the difference between the transfer mode ratio and 1. For example, when the transfer mode ratio is greater than 1, compensation network 26E may function to increase inductance, and the amount of increase in inductance may increase as the transfer mode ratio increases above 1. Similarly, when the transfer mode ratio is less than 1, compensation network 26E may function to increase capacitance, and the increase in capacitance may increase as the transfer mode ratio decreases above 1.

[0258] In some embodiments, compensation network 26E may be configured to modulate the signal provided to transmitter resonator 30 with information, thereby functioning as a source transmit modulator. The information for modulating the signal provided to transmitter resonator 30 may be provided to compensation network 26E by controller 22, and the information may comprise control data directed to controller 42 of receiver module 40 via receiver resonator 50, controller 42 being described in more detail below with reference to FIG. 7. In yet another embodiment, oscillator 26A may function as a source transmit modulator. The modulation employed by the selected source transmit modulator may be any one of amplitudes. Modulation. Frequency modulation. Phase modulation. Information may be modulated onto the signal provided to the transmitter resonator 30 in digital or analog form. The information may be modulated onto the resonant frequency of the power signal provided to the transmitter resonator 30 by the source transmitter modulator. In other embodiments, the information may be modulated at a frequency different from the frequency of power transmission. In other embodiments, the information may be modulated onto a harmonic of the resonant frequency of the power signal provided to the transmitter resonator 30, while in further embodiments, the resonant frequency of the power signal provided to the transmitter resonator 30 may be a harmonic of the frequency of the signal onto which the information is modulated. The V / I tuner 26F, described in more detail below, may be configured to transmit an information signal to the transmitter resonator 30, thereby being transparent with respect to the information being transmitted. Information transmitted in the manner described herein may include, but is not limited to, the operating mode of the module 20, the number and type of receivers 40, ambient object sensor information, and load status monitoring information, including, for example, battery state of charge, load voltage, and load current.

[0259] An embodiment of V / I tuner 26F is shown in more detail in Figure 10. The input signal of V / I tuner 26F received from matching network 26E (Figure 6) is split by splitter 262 to have two mutually asymmetric paths 261A and 261B for the input signal. First phase shifter 264A and second phase shifter 264B generate a phase difference between the input voltage and the input current of transmitter resonator 30 (Figure 6). First phase shifter 264A is controlled by controller 22 (Figure 6) via first phase splitter control line 262A, and second phase shifter 264B is controlled by controller 22 (see Figure 6) via second phase splitter control line 263B. The first and second active switches 26A and 266B receive signals from the first and second phase shifters 264A and 264B, respectively, and are controlled by the controller 22 via first and second active switch control lines 265A and 265B. The first and second active switches 26A and 266B are responsible for conditioning the imaginary parts of the signals received from the first and second phase shifters 264A and 264B, respectively. Passive signal shaping networks 268A and 268B receive the conditioned signals from the first and second active switches 266A and 266B, respectively. The passive signal shaping networks 268A and 268B are responsible for fine-tuning the signals received from the first and second active switches 26A and 266B, respectively, and in some embodiments, for reducing any harmonics in the signals before passing them to the combiner. 269. The signals provided along the two mutually asymmetric paths 261A and 261B are combined by combiner 269 and provided to transmitter resonator 30; in other embodiments, first and second phase shifters 264A and 264B may be combined as one phase shifter that receives the input signal to V / I tuner 26F, and the combined phase shifter may have two separate outputs that serve active switches 266A and 266B.

[0260] V / I tuner 26F adjusts the transfer mode ratio by adjusting the phase difference between the input current and input voltage to transmitter resonator 30 in response to signals from controller 22; the real part of the impedance seen by transmitter module 20 can be adjusted by phase shifters 264A and 264B, and its imaginary part can be adjusted by switches 266A and 266B. For example, a 90 degree phase shift can be made every 10 milliseconds, resulting in 30% magnetic power transfer and 70% electrical power transfer.

[0261] The V / I tuner 26F may be configured to adjust the current through each transmitter antenna (e.g., the first and second transmitter antennas 32, 132, 232, 332, 134, 234, 334 or the third transmitter antenna 336) and the potential applied to each transmitter antenna (e.g., the first and second transmitter antennas 32, 132, 232, 332, 134, 234, 334 or the third transmitter antenna 336).

[0262] When current is passed through both the first and second transmitter antennas 132, 134, they each generate a magnetic field 31A for IPT purposes. When the current supplied to the second transmitter antenna 134 is reduced compared to the current supplied to the first transmitter antenna 132, a potential difference is created between the first and second transmitter antennas 132, generating an electric field 3IB for CPT purposes. To modulate between CPT and IPT, the current delivered to the second antenna 134 can be modulated (e.g., when less current is allowed to pass through the second antenna 134, less IPT will occur, and when more current is allowed to pass through the second antenna, more CPT will occur). For example, when it is desired to transfer power via IPT, the I / V tuner 26F can be configured to act as a short circuit connecting the first and second transmitter antennas together, thereby creating a series LC resonator that allows current to flow therethrough. Conversely, when it is desired to transfer power via CPT, the I / V tuner 26F may be configured to act as an open circuit to dump current, thereby creating a potential difference between the first and second transmitter antennas 132, 134. The I / V tuner 26F may be configured to thereby control whether the first and second transmitter antennas 132, 134 are effectively connected in series or in parallel.

[0263] Alternatively, when the first and second transmitter antennas 132, 134 are connected in parallel, the first and second transmitter antennas 132, 134 may be floated so that an electric field 3IB is generated for CPT purposes without generating a substantially magnetic field 31A. To change the transfer mode ratio (e.g., to modulate between CPT and IPT), the I / V tuner 26F may be configured to alternate (such as by a multiplexer in the I / V tuner 26F) between the floating first and second transmitter antennas 132, 134 to drive current through the first and second transmitter antennas 132, 134 to induce CPT and IPT. The alternation may be performed in milliseconds or at a frequency between 10 Hz and 10 kHz. If more time is allocated to the floating first and second transmitter antennas 132, 134, the transmission mode ratio will be biased towards more CPT, and if more time is allocated to the drive current through the first and second transmitter antennas 132, 134, the transmission mode will be biased towards more IPT.

[0264] In some embodiments, elements 26 may be separate elements within transmitter module 20, while in other embodiments, one or more of elements 26 may be part of an integrated circuit design.

[0265] FIG. 7 is a schematic diagram of a load 70 and secondary side 14 (shown in FIG. 1) including a receiver resonator 50 and a receiver module 40, according to some embodiments.

[0266] Receiver resonator 50 may comprise any of receiver resonators 50, 150, 250, 350, or may be otherwise described herein. Receiver resonator 50 may be configured to capture power at a frequency set by an oscillator signal in transmitter module 20, for example, without limitation, between 1 MHz and 1 GHz. The frequencies set by the oscillation signal of the transmitting module 20 are approximately 1 MHz to approximately 100 MHz, approximately 1 MHz to approximately 200 MHz, approximately 1 MHz to approximately 300 MHz, approximately 1 MHz to approximately 400 MHz, approximately 1 MHz to approximately 500 MHz, approximately 1 MHz to approximately 900 MHz, approximately 1 MHz to approximately 1 GHz, approximately 100 MHz to approximately 200 MHz, approximately 100 MHz to approximately 300 MHz, approximately 100 MHz to approximately 400 MHz, approximately 100 MHz to approximately 500 MHz, approximately 100 MHz to approximately 600 MHz, approximately 100 MHz to approximately 700 MHz, approximately 100 MHz to approximately 800 MHz, approximately 100 MHz to approximately 900 MHz, approximately 100 MHz to approximately 1 GHz. About 1G Hz, About 200M Hz - About 300M Hz, About 200M Hz - About 400M Hz, About 200M Hz - About 500M Hz, About 200M Hz - About 600M Hz, About 200M Hz - About 700M Hz, About 200M Hz - About 800M Hz, About 200M Hz - About 900M Hz, about 200M Hz - about 1G Hz, about 300M Hz - about 400M Hz, about 300M Hz - about 500M Hz, about 300M Hz - about 600M Hz, about 300M Hz - about 700M Hz, about 300M Hz - about 800M Hz, about 300M Hz - about 900M Hz, about 300M Hz - approx. 1G Hz, about 400M Hz - about 500M Hz, about 400M Hz - about 600M Hz, about 400M Hz - about 700M Hz, about 400M Hz - about 800M Hz, about 400M Hz - about 900M Hz, about 400M Hz - about 800M Hz, about 500M Hz - about 900M Hz, about 500M Hz - about 1G Hz, about 600M Hz - about 700M Hz, about 600M Hz - about 800M Hz, about 600M Hz - about 900M Hz, about 600M Hz - about 1G Hz, about 700M Hz - about 800M Hz, about 700M Hz - about 900M Hz, about 700M Hz - about 1G Hz, about 800M Hz to about 900 MHz, about 800 MHz to about 1 GHz, or about 900 MHz to about 1 GHz. In some embodiments, the frequency set by the oscillator signal in transmitter module 20 is about 1 MHz, about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, about 900 MHz, or about 1 GHz.In some embodiments, the frequency set by the oscillating signal in transmitter module 20 is, in some embodiments, at least about 1 MHz, about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, or about 900 MHz, and the frequency set by the oscillating signal in transmitter module 20 is, in some embodiments, at most about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, about 900 MHz, or about 1 GHz.

[0267] In some applications, frequencies in the Industrial, Scientific, and Medical (ISM) frequency band may be preferred. For purposes of this disclosure, the ISM band should be understood to be 6.765 MHz-6.795 MHz, 13.553 MHz-13.567 MHz, 26.957 MHz-27.283 MHz, 40.66 MHz-40.70 MHz, 83.996 MHz-84.004 MHz, 167.992 MHz-168.008 MHz, 433.05 MHz-434.79 MHz, and 886 MHz-906 MHz. The receiver resonator 50 may be configured to capture power from the magnetic field 31A or the electric field 3IB, or any combination of these two fields at that frequency.

[0268] The receiver module 40 includes a controller 42 configured to receive various inputs from sensors 44 (e.g., a receiver power sensor 44A and a load detector 44B) and output control signals to various elements 46 (e.g., a compensation network 46A, a matching network 46B, a rectifier 46D, a filter 46C, and a load manager 46E).

[0269] The receiver power sensor 44A can measure the power (eg, measure the current and voltage) at point 44C to determine how much power is being received by the receiver resonator 50.

[0270] The load detector 44B is configured to detect the presence of a load, which may be implemented using a physical sensor (for example, but not limited to, a light sensor, a pressure sensor, an infrared sensor, or a proximity sensor). This may be done by or with appropriate software or firmware. In the example of Lor, in some embodiments, the current and voltage may be measured by the load detector 44B, for example, at point 44D, to determine the power being received by the load 50; if the amount of power being measured at point 44D increases above the baseline, the load detector 44B may signal to the controller 42 that a load 70 is present.

[0271] The compensation network 46A may be configured to maintain a desired resonant frequency of the receiver resonator 50 in response to a signal from the controller 42, thereby improving the efficiency of power transfer from the transmitter resonator 30 to the receiver resonator 50. Compensation network 46A may be a substantially similar compensation network 26E of transmitter module 20 and may function substantially similarly.

[0272] Matching network 26D may be configured to adjust the input impedance of rectifier 46D to match the desired impedance of resonator 30 to achieve maximum power transfer.

[0273] The rectifier 46D may be configured to convert the AC power received by the receiver antenna 50 to DC power for supply to the load 70.

[0274] The filter 46C may be configured to shape the waveform of the power output from the rectifier 46D according to a signal from the controller 42 to improve the overall power efficiency of the receiver module 40.

[0275] The load manager 46E may be configured to provide a suitable voltage and current to the load 70 and / or to extract maximum power from the rectifier 46D by adjusting its input impedance (e.g., the output impedance of the rectifier 46D).

[0276] In some embodiments, the load manager 46E or another component may be configured to communicate (wirelessly or wired) with an external device (e.g., the load 70) to provide information suitable for data analysis. Such information may include, for example, but not limited to, the presence of the load 70, the charge level of the load 70, the charge rate of the load 70, the state of the load 70, the current voltage, capacity, and / or the time remaining to charge the load 70. The load manager 46E may use such information (or relay such information to the controller 42 or 22), for example, to adjust the transfer mode ratio to achieve optimal energy transfer between the primary side 12 and the secondary side 14. The load manager 46E may also provide such information to a user via a display. Such a display may be incorporated into one or more of the primary side 12 and the secondary side 14 or may be accessible via software on a mobile device, such as an app on a mobile phone or tablet, in wireless (or wired) communication with the load manager 46E or the controller 22 or 42.

[0277] In some embodiments, components 46 are separate elements within receiver module 40, while in other embodiments, one or more of components 46 are part of an integrated circuit design.

[0278] In some embodiments, the primary side 12 may include multiple transmitter resonators 30, and / or the secondary side 14 may include multiple receiver resonators 50. In such embodiments, each of the transmitter resonators 30 and / or receiver resonators 50 may be controlled in a similar manner. In other embodiments, each of the transmitter resonators 30 and / or receiver resonators 50 may be controlled individually. For example, in some embodiments, the primary side 12 may rely more heavily on a receiver resonator 50 that is more efficiently and / or similarly transmitting power, or experiencing less interference (e.g., due to nearby metal objects), while the secondary side 14 is more efficiently receiving power, or receiving power more efficiently. Such control may be provided or facilitated, for example, by the transmitter module 20 and the receiver module 40, and / or communication therebetween.

[0279] 9 is a schematic diagram of a rectifier 46D with an integrated phase shifter. In some embodiments, the rectifier 46D comprises a separate phase shifter.

[0280] The rectifier 46D may be a switch-mode self-synchronous rectifier (single-ended mode or differential configuration) that may be configured to receive a sinusoidal wave (e.g., AC power) from the receiver resonator 50 at a particular resonant frequency. The rectifier 46D may be a differential switch-mode self-synchronous rectifier. The rectifier 46D may capture sufficient power from the receiver resonator 50 so that the E field or the H field, or any combination of the E and H fields, may be captured by the receiver resonator 50.

[0281] Rectifier 46D has an input 147A (e.g., AC power) that drives an active device 147B (e.g., a transistor) with a frequency set at the resonant frequency, and an output 147D (e.g., DC voltage) across a DC load (used to control the active device's output power, input impedance, and operating range). In this design, different load terminations are used to improve performance (e.g., output power and power conversion efficiency). A third harmonic termination 147D is placed in a series branch at the drain to shape the voltage waveform at node 147E. A second harmonic termination 147F is placed in a parallel branch at the drain to shape the voltage waveform at node 147E. A first harmonic termination 147G is placed in a series branch at the drain to shape the voltage waveform at node 147E. The effect of the third harmonic termination can be considered in both the second and first harmonic terminations. The effect of the second harmonic termination can be considered in the first harmonic termination.

[0282] In a differential configuration, the AC source 147A is placed in series with the receiver resonator 50. The AC source 147A may be a function of the power received by the receiver resonator 50, and the alignment and position of the receiver resonator 50 relative to the transmitter resonator 30C may be a single-ended load.

[0283] The rectifier 46D may include two phase shifters 147H in a differential configuration (but only one phase shifter in a single-ended configuration). The phase shifter 147H adjusts the appropriate phase difference between the AC source and the gate signal of the transistor 147B. The phase difference between the gate signal and the AC source 147A can change the self-synchronous linearity performance (e.g., the power conversion efficiency and operating range of the transistor). It can also change the input impedance of the self-synchronous rectifier 46D and / or the optimal DC load 147C of the rectifier 46D.

[0284] The rectifier 46D may include two level shifters 1471 in a differential configuration (but only one level shifter in a single-ended configuration). The level shifter 1471 may adjust the appropriate amplitude for the gate signal of the transistor 147B. The amplitude level of the gate signal may change the linear performance of the self-clocking (e.g., the power conversion efficiency and operating range of the transistor).

[0285] The rectifier 46D may be reconfigurable to function as an amplifier. As part of such reconfiguration, the integrated phase shifter 147H and the integrated level shifter 1471 (see FIG. 9 ) may be adjusted to enable the rectifier 46D to function as an amplifier based on the inherent amplification and switching functions of the transistor 147B. This reconfigurability of the rectifier 46D between operating as a rectifier and as an amplifier allows the receiver module 40 to be controllably reconfigured between receiver mode and transmitter mode, respectively. The reconfiguration may be performed under instructions from the controller 422; when the rectifier 46D is reconfigured from a rectifier to an amplifier, the AC source 147A changes to an AC load 147A, and when the rectifier 46D is reconfigured from a rectifier to an amplifier, the DC load 147C is reconfigured to a DC source.

[0286] In some embodiments, when the receiver module 40 is in transmitter mode, the compensation network 46A may be configured to modulate the signal provided to the resonator 50 with information, thereby functioning as a source transmit modulator. The information for modulating the signal provided to the resonator 50 may be provided to the compensation network 46A by the controller 42. The information may comprise control data directed to the controller 22 of the transmitter module 20 via the resonator 30. In some embodiments, when the receiver module 40 is in transmitter mode and the rectifier 46D is configured as an amplifier, the amplifier 46D may act as a modulator for the module 40. The modulation used may be any one of amplitude modulation, frequency modulation, phase modulation, and combinations thereof. The information may be modulated onto the signal provided to the transmitter resonator 50 in digital or analog form. The information may be modulated onto the resonant frequency of the power signal provided to the transmitter resonator 50 by the source transmit modulator. In other embodiments, the information may be modulated at a frequency different from the frequency of the power transfer. In other embodiments, the information may be modulated onto a harmonic of the resonant frequency of the power signal provided to the transmitter resonator 50, while in further embodiments, the resonant frequency of the power signal provided to the transmitter resonator 50 may be a harmonic of the frequency of the signal onto which the information is modulated. Information transmitted in the manner described herein may include, for example, but is not limited to, the presence of the load 70, the charge level of the load 70, the power transfer efficiency, the charge rate of the load 70, the state of the load 70, the current voltage, the charge capacity, and the time remaining to charge the load 70.

[0287] Having described how both module 20 and module 40 can be reconfigured between transmitter and receiver modes, and how signals from both module 20 and module 40 can be modulated, it will be apparent that system 10 of FIG. 1 can include additional secondaries similar to secondary 14 of FIGS. 1 and 7, and when additional secondaries are present, the above configuration enables communication of information between the various secondaries.

[0288] In some embodiments, the primary side 12 and secondary side 14 may communicate via signal frequencies similar to Bluetooth (e.g., 2.4 GHz) or GPS (e.g., 10 GHz). In some embodiments, there may be additional units that may separately collect data and transfer data back and forth between the primary side 12 and / or secondary side 14, and in some embodiments, WiFi may be employed to upload data from the primary side 12 and / or secondary side 14 to an online portal (e.g., a website or mobile application associated with the primary side 12 and / or secondary side 14).

[0289] In some embodiments, it may be desirable to transfer power between two receiver modules 40 (e.g., peer-to-peer power transfer). For example, if a first e-bicycle with a first receiver has a dead or low battery and a second e-bicycle with a second receiver and at least a partially charged battery is nearby, it may be desirable to transfer power from the second e-bicycle to the first e-bicycle. Such a situation may be relevant, for example, when no transmitter is nearby. The provision of at least one of the two receiver modules 40 involved in reconfiguring to a transmitter module enables such peer-to-peer power transfer. Generally, it enables the transfer of power between multiple secondaries 14.

[0290] In other embodiments, it may be necessary to transmit power in the reverse direction, i.e., from the load side to the source side in FIGS. 1, 6, and 7, at certain times. The ability of both module 20 and module 40 to be reconfigured between operating in transmitter and receiver modes allows for such a transfer of power in the reverse direction, from module 40 to module 20. Thus, the system allows for bidirectional power transfer. Given the fact that devices 26B and 46D in FIGS. 8 and 9 can be reconfigured to function as amplifiers or rectifiers, respectively, these devices may be collectively referred to as a differential self-synchronous radio frequency power amplifier / rectifier. Given the bidirectional nature of power transmission, both transmitter resonator 30 and receiver resonator 50 may be described as transmitter-receiver resonators, and both modules 20 and 40 may be referred to as power transmission modules. Such a configuration is useful in electric vehicles, where kinetic energy needs to be converted and transferred to a battery during braking. Other systems, conditions, and configurations where such a changed direction of power transmission applies include, for example, but not limited to, several mobile phones that may have different levels of battery life and can be used to at least partially recharge each other. In the more general case, when both the transmitting and receiving systems do not have a permanent energy source, e.g., grid power, the bidirectional capability can be used to transfer energy in either direction.

[0291] In a further aspect described with respect to FIG. 31 , a near-field radio frequency method for transferring power via a power signal at a power signal frequency is provided, the method including providing a bimodal resonant near-field radio frequency power transfer system comprising a plurality of power transmit-receive modules, wherein: The plurality of power transmission / reception modules are in wired communication with a transmitter resonator arranged to exchange power with at least one of the plurality of power transmission / reception modules, and the power transfer system is operated for simultaneous capacitive power transfer and inductive power transfer according to an adjustable transfer mode ratio.

[0292] Providing the power transmission system may include providing a first power transmission receiving module of a plurality of power transmitting and receiving modules having a power signal tuner module, and operating the power transmission system may include changing the transmission mode ratio by adjusting the power signal tuner module.

[0293] Providing a power transmission system may comprise providing at least one power transmit-receive module among a plurality of power transmit-receive modules in wired communication with an associated transmitter-receiver resonator and having a modulator; and operating the power transmission system, wherein operating the power transmission system may comprise exchanging radio frequency signals between the associated transmitter-receiver resonator and a transceiver resonator in wired communication with at least one of the plurality of power transmit-receive modules; and modulating information onto the exchanged radio frequency signals. When a power load is present at an output of one of the plurality of power transmit-receive modules, the information modulated onto the exchanged signals may include, for example, but is not limited to, one or more of: presence of the power load, charge level of the power load, power transfer efficiency, charge rate of the power load, state of the power load, presence of voltage across the power load, charge capacity of the power load, and remaining time to charge the power load.

[0294] The information may be modulated onto the exchanged radio frequency signals by amplitude modulation, frequency modulation, or phase modulation. Modulating information onto the exchanged radio frequency signals may include modulating digital information or analog information onto the exchanged radio frequency signals.

[0295] Modulating the information onto the exchanged radio frequency signal can include modulating the information onto an electrical power signal. Modulating the information onto the exchanged radio frequency signal can include modulating the information onto a signal having a frequency different from the electrical power signal frequency. The exchanged radio frequency signal may include modulating the information onto a signal having a frequency that is a harmonic of the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having the power signal frequency as a harmonic.

[0296] Modulating information onto the exchanged radio frequency signals may include modulating according to a reflection characteristic of an associated wired transmitter-receiver resonator to impose information on a signal reflected by the wired transmitter-receiver resonator. Modulating information onto the exchanged radio frequency signals may include modulating according to a signal provided to the associated transmitter-receiver resonator.

[0297] The method may include operating a power signal tuner module of a first power transmit receive module of the plurality of power transmit receive modules to modulate information onto the exchanged radio frequency signal. Each of the provided power transmit receive modules may include a compensation network, which may include a modulator, allowing the compensation network to be operated to modulate information onto the exchanged radio frequency signal. At least one of the power transmit receive modules may include a radio frequency oscillator that provides a signal at the power signal frequency to the at least one power transmit receive module, which may include a modulator, allowing information to be modulated onto the exchanged radio frequency signal in the oscillator.

[0298] Each of the plurality of power transmit-receive modules may be reconfigurable between a power transmitter mode and a power receiver mode, and the method may further include reconfiguring at least two of the plurality of power transmit-receive modules between a power transmitter mode and a power receiver mode to reverse the direction of power transmission between the at least two transmit-receive modules. Each of the plurality of power transmit-receive modules may include a differential self-synchronous radio frequency power amplifier / rectifier reconfigurable between an amplifier condition and a rectifier condition corresponding to the power transmitter mode and the power receiver mode of the power transmit module, respectively, and the method may include reconfiguring the differential self-synchronous radio frequency power amplifier / rectifier of the at least two transmit-receive modules between the amplifier condition and the rectifier condition. Each differential self-synchronous radio frequency power amplifier / rectifier may include an adjustable phase shifter to reconfigure the differential self-synchronous radio frequency power amplifier / rectifier between the amplifier condition and the rectifier condition, and the method may include adjusting the phase shifter of each of the differential self-synchronous radio frequency power amplifier / rectifier of the at least two transmit-receive modules.

[0299] The WPT system 10, including the transmitters and / or receivers described herein, can be integrated into a variety of applications, such as, but not limited to, electric vehicles, electric boats, electric planes, electric trucks, e-bikes, electric scooters, electric skateboards, and an exemplary non-limiting application is a bike-sharing fleet, where various docking stations equipped with receivers (e.g., secondary side 14) and batteries (as loads 70) can be charged at the docking stations.

[0300] In some applications, the primary 12 or secondary 14 may be configured to transfer power with other systems not described herein, and the CPT to IPT transfer mode ratio may be adjusted to provide compatibility with other CPT and / or IPT systems even if not specifically designed to operate with the power transfer systems described herein.

[0301] While several exemplary aspects and embodiments have been described above, those skilled in the art will recognize several modifications, permutations, additions, and subcombinations thereof. Accordingly, it is intended that the following appended claims and the claims introduced below be interpreted to include all such modifications, permutations, additions, and subcombinations consistent with the broadest interpretation of the entire specification.

[0302] In a first aspect, each of the system(s) described above and shown in FIGS. 1-10 form a bimodal near-field resonant wireless power transfer system 10 configured for simultaneous capacitive and inductive power transfer according to an adjustable transfer mode ratio at a variable resonant power signal oscillation frequency, the system 10 including a transmitter antenna subsystem 32, 132, 232, 332 134, 234, 334, 336 and a power signal tuner module 26F, the tuner module 26F configured to adjust the transfer mode ratio by adjusting the power signal provided by the tuner module 26F to the transmit antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336; a receiver subsystem 14 comprising receiver antenna subsystems 52, 152, 252, 352, 154, 254, 354, 356 configured to receive power from the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 at the transfer mode ratio;

[0303] The tuner module 26F may be configured to adjust the power signal by adjusting a phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336, and the controller 22 is configured to receive sensor information from the at least one sensor 24 and automatically provide tuning instructions to the tuner module 26F based on the sensor information; the tuner module 26F is configured to adjust the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 in accordance with the tuning instructions.

[0304] The system 10 resonates at a resonant frequency that varies freely within a predetermined band based on the degree of coupling between the transmitter subsystem 12 and the receiver subsystem 14. The predetermined band may be, by way of example and not limitation, a formally designated and reserved Industrial, Scientific, and Medical (ISM) band or a user-dedicated band. The quality factor (Q) of the system 10 may be reduced to an extent that allows the power signal oscillation frequency to vary within the opposite limits of the predetermined frequency band. The reduced value of Q allows the system 10 to use any of several different resonant frequencies within the predetermined frequency band during the power transfer process. The coupling between the transmitter subsystem 12 and the receiver subsystem 14, and the associated absorption of power by the resonant receiver subsystem 14, ensures that most electromagnetic radiation is emitted into the far-field region when the system 10 is operating. The configurations described herein with reference to Figures 1-10, together with the aforementioned frequency aspects, render the system 10 a bimodal near-field resonant wireless power transfer system. Note that in the wireless power transfer system 10, power is transferred from the primary subsystem to the secondary subsystem via capacitive or inductive coupling or both, and not to a substantial extent via electromagnetic radiation.

[0305] In a further aspect described with reference to the foregoing drawing and flowchart of FIG. 11 , a near-field wireless method is provided for bidirectionally transferring power according to an adjustable transfer mode ratio at a variable resonant power signal oscillation frequency, the method comprising: providing a transmitter subsystem 12 comprising a power signal tuner module 26F and a transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 configured to resonate at the resonant power signal oscillation frequency; providing a receiver subsystem 14 comprising a receiver antenna subsystem 52, 152, 252, 352, 154, 254, 354, 356 configured to resonate at the resonant power signal oscillation frequency; and providing a power signal from the tuner module 26F to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 at the power signal oscillation resonant frequency. and receiving the transferred power at the receiver subsystem 14 at the power signal oscillation resonant frequency via the receiver antenna subsystem 52, 152, 252, 352, 154, 254, 354, 356 at the transfer mode ratio. Adjusting the transfer mode ratio may include adjusting a phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336.

[0306] Providing the transmitter subsystem 12 may further include providing a controller 22 and at least one sensor 24, and may be performed by the tuner module 26F via a command of the controller 22 based on sensor information received from the at least one sensor 24 by the controller 22, and the command of the controller 22 may be automatically issued to the tuner module 26F upon receipt by the controller 22 of the sensor information, and the tuner module 26F may automatically execute the command from the controller 22 to change the phase difference.

[0307] The method may further include allowing the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an industrial, scientific, and medical (ISM) frequency band. Providing the transmit subsystem may include providing a transmitter subsystem that is detuned to an extent that allows the resonant power signal oscillation frequency to vary within opposite limits of the predetermined frequency band.

[0308] In a further embodiment described with reference to FIGS. 1-10 and with reference to FIGS. 12, 13A, and 13B, a multi-transmitter bimodal near-field resonant wireless power transfer system 10′ is configured for simultaneous capacitive and inductive power transfer according to an adjustable transfer mode ratio at a variable resonant power signal oscillation frequency. The system 10′ includes a multi-transmitter subsystem 12′ including multiple transmit resonators 30A′-30F, each driven by a corresponding dedicated transmit module 20A′-20F, where each transmitter resonator and corresponding transmit module (e.g., 30E′ and 20E′, respectively) may conform to the description provided above with reference to FIGS. 1-10. FIG. 12 is a schematic diagram of an embodiment of the system 10′ in which the transmit resonators 30A′-30F are presented as nine resonators in a row, but their formal spatial locations are not shown. One embodiment of the spatial layout of the multi-transmitter subsystem 12′ is shown in FIGS. 13A and 13B and described below. In system 10′, resonant receiver subsystem 14 may be the same as or substantially similar to the resonant receiver system described above and referenced by FIGS. 1-10; in the embodiment shown in FIG. 12, resonant receiver subsystem 14 may be implemented, for example, without limitation, within a mobile phone or digital tablet. Resonant receiver subsystem 14 is depicted in dashed lines in FIG. 13A for clarity. In one embodiment, each working transmit resonator 30A′-30F and each corresponding transmit module 20A′-20F may function in the same or substantially similar manner as the transmit resonator 30 and transmit module 20 described above and shown in FIGS. 1-10; an embodiment of the spatial layout of multi-transmit subsystem 12′ is shown in FIGS. 13A and 13B. FIG. 13B is a view of multi-transmit subsystem 12′ in an inverted orientation relative to that of FIG. 13A.

[0309] In the exemplary embodiment of system 10′ shown in Figures 12, 13A, and 13B, multi-transmit subsystem 12′ comprises nine pairs of transmitter resonators 30A′-30F and corresponding transmitter modules 20A′-20F arranged in a square array. Transmitter modules 20A′-20F are visible in Figure 13A, although they are obscured by a grounded base plate 35′. 13B. In more general embodiments, other numbers of resonator and transmitter module pairs may be used, and the resonator array need not be square or rectangular. By way of example and not limitation, the resonator array may have a hexagonal arrangement. In some embodiments, the array is preferably densely packed within the constraints of a grounded shield grid that separates and bounds the transmitter resonators 30A'-301'. The ground shield grid 33' laterally confines the array of transmitter resonators 30A'-301'. The ground shield grid 33' is positioned a consistent distance 37' from the periphery of each of the transmitter resonators 30A'-301' to ensure consistent electric field behavior and associated capacitance between the transmitter resonators 30A'-301' and the ground shield grid 33'. The term "shield distance" is used herein to describe this distance between the resonators 30A'-301' and the ground shield grid 33'.

[0310] In one embodiment, ground shield grid 33' ensures that the electric fields of transmitter resonators 30A'-30T are completely spatially separated and thereby spatially independent. The transmitter resonators 30A'-30T may have magnetic fields that are selected to be separated from one another by spatial orientation. In other embodiments, the ground shield grid 33' may be formed from or coated with a high conductivity ferrite material to separate the magnetic fields generated by the transmitter resonators 30A'-30T.

[0311] As shown in FIGS. 13A and 13B, the transmitter resonators 30A'-30T and their corresponding transmitter modules 20A'-201' may be mounted substantially in-line with one another on opposing sides of a grounded base plate 35', with each transmitter resonator (e.g., 30E') adjacent to its corresponding transmitter module (20E'). In other embodiments, there may not be a fixed spatial relationship between the transmitter resonators and their corresponding transmitter modules. The array of transmitter resonators 30A'-30T may share a common transmit plane defined by the collective top surfaces of the transmitter resonators 30A'-30T in FIG. 13A for aesthetic and protective reasons, and the array of transmitter resonators 30A'-30T may be covered with a dielectric plate (not shown in FIG. 13A). The dielectric plate separates the receiver subsystem 14 and the transmitter resonators 30A'-301'.

[0312] 12 and 13A, an embodiment of the resonant receiver subsystem 14 is shown schematically as overlapping a subset of the plurality of transmitter resonators 30A'-301'. As in FIGS. 12 and 13A, the overlapping transmitter resonators are shown as 30D', 13A, the resonant receiver subsystems 14 are shown as dashed rectangles across adjacent transmitter resonators 30D', 30E', ​​30G', and 30H'. The controller of any of the transmitter modules 20A'-20F can determine the presence or absence of a resonant receiver subsystem 14 adjacent to or overlapping its corresponding transmitter resonator 30A'-30F, and based on these detections, the controller can turn on or off a power signal to its corresponding transmitter resonator 30A'-30F.

[0313] If the power amplifiers of transmitter modules 20A'-201' provide power signals to transmitter resonators 30A'-301' so that transmitter resonators 30A'-301' transmit power, and the controllers of transmitter modules 20A', 20B', 20C', 20F' and 201' determine that there are no resonating receivers within their frequency ranges proximate to transmitter resonators 30A', 30B', 30C', 30F' and 301', then those controllers can turn off the power signals to transmitter resonators 30A', 30B', 30C', 30F' and 301'.

[0314] When the power amplifiers of transmitter modules 20A'-201' are not supplying power signals to transmitter resonators 30A'-30F, the controllers for transmitter resonators 30D', 30E', ​​30G', and 30H' can determine the presence of resonant receiver subsystems 14 that overlap with resonators 30D', 30E', ​​30G', and 30H' and turn on the transmittable power provided by transmitter modules 20D', 20E', 20G', and 20H' to transmitter resonators 30D', 30E', ​​30G', and 30H'. This configuration ensures that only transmitter resonators proximate to a resonant receiver subsystem 14 draw power and transmit power to the resonant receiver subsystem 14.

[0315] The input impedance of the transmitter resonator 30A'-301' can be used to detect the presence or absence of a resonant receiver subsystem 14 proximate to the transmitter resonator. The transmitter resonator input impedance changes depending on the presence or absence of a resonant receiver subsystem 14 proximate to the transmitter resonator. As explained above, with reference to FIG. 6, the effect of a particular resonant receiver subsystem 14 can not only allow the presence or absence of a receiver to be detected, but also characteristics such that the type of receiver can be identified by its effect on the transmitter resonator input impedance. The size of the receiver resonator, in some embodiments, has a discovered effect on the input impedance of the transmitter resonator 30A'-301'.

[0316] In one embodiment of the system 10', as shown in Figures 12 and 13B, transmitter module 20E' is a transmitter module associated with one of four transmitter resonators 30D', 30E', ​​30G' and 30H' overlapped by the resonant receiver subsystem 14, and the detailed structure of each of the transmitter modules 20A'-201' begins with the power amplifier 26B of the transmitter module 20A'-201', which does not provide a power signal to the corresponding transmitter resonator 30A'-301'.

[0317] Focusing now on the transmitter module 20E', its load detector 24A in this embodiment is configured to measure the input impedance of the transmitter resonator 30E'. The load detector 24A provides the input impedance measurement to the controller 22. A default input impedance measurement is stored in a register within the controller 22 representing the input impedance of the transmitter resonator 30E' in the absence of a resonating receiver subsystem proximate to the transmitter resonator 30E'. As shown in FIG. 12, placement of the resonating receiver subsystem 14 proximate to the transmitter resonator 30E' leads to a new, different input impedance measurement by the load detector 24A, the result of which is provided by the load detector 24A to the controller 22. The controller 22 compares the new input impedance measurement, referred to herein as a first input transmitter resonator impedance change or primary transmitter resonator input impedance change, with the default impedance measurement stored in the register. Based on this first input impedance change, the controller 22 makes a determination as to whether a receiver resonator, e.g., the resonator of the resonating receiver subsystem 14, is present proximate to the transmitter resonator 30E'. To determine the absence or presence of a receiver resonator adjacent to the transmitter resonator 30E' controller 22 can be preprogrammed with a minimum input impedance change that must be exceeded before the controller 22 considers a receiver resonator to be present.

[0318] If the controller 22 determines that a receiver resonator, e.g., the resonator of the resonant receiver subsystem 14, is present in close proximity to the transmitter resonator 30E', ​​the controller 22 commands the power amplifier to assume an "on" state, whereby power is supplied to the transmitter resonator 30E' and power is transferred to the resonant receiver subsystem 14; if the controller 22 determines that a receiver resonator, e.g., the resonator of the resonant receiver subsystem 14, is not present in close proximity to the transmitter resonator 30E', ​​the controller 22 commands the power amplifier to assume an off state, whereby no power is supplied to the transmitter. The power is then not transferred to the resonant receiver subsystem 14, and the same process is performed independently by all transmitter modules 20A'-201' with respect to their corresponding transmitter resonators 30A'-30T. As a result, the power amplifiers of transmitter modules 30D', 30E', ​​30G', and 30H' that are overlapped by the resonant receiver subsystem 14 are turned on, and the power amplifiers of transmitter modules 30A', 30B', 30C', 30F', and 30T that are not overlapped by the resonant receiver subsystem 14 are turned off.

[0319] Note that different sized receiver resonators present significantly different impedances to the load detector 24A of the transmitter module 20 at point 24A. This allows the controller 22 of any transmitter module 20A'-20T to distinguish between small and large receiver resonators that are in close proximity to the corresponding transmitter resonator 30A'-30T.

[0320] According to one embodiment, described herein is the setting of power signal frequency and phase between transmitter resonators (e.g., 30D', 30E', ​​30G', and 30H') that are overlapped by a resonant receiver subsystem, such as resonant receiver subsystem 14. For maximum efficiency transfer of power from the combination of transmitter resonators 30D', 30E', ​​30G', and 30H' that are receiving power, the power signals in resonators 30D', 30E', ​​30G', and 30H' should have the same frequency and should be in phase with each other. Considering that the frequencies of the power signals in transmitter resonators 30D', 30E', ​​30G' and 30H' may differ within a tolerance band, as discussed above with reference to Figures 1-10, a requirement in this embodiment of Figures 12, 13A and 13B is for the frequencies of the power signals in transmitter resonators 30D', 30E', ​​30G' and 30H' to be adjusted so that the power signals from transmitter resonators 30D', 30E', ​​30G' and 30H' are perfectly synchronized and in phase.

[0321] In one embodiment, to ensure that the controllers 22 of overlapping transmitter resonators 30D', 30E', ​​30G', and 30H' all set their corresponding oscillators 26A to the same frequency, the controllers 22 of transmitter modules 20A'-201' are all given the same table of selected frequencies within any given tolerance band, e.g., the ISM band, within that ISM. A number of discrete frequencies are selected for inclusion in the frequency table. Thus, the number of tabulated frequencies within the ISM band is finite and limited, and the tabulated frequencies are spaced far enough apart that the various controllers 22 of transmitter modules 20D', 20E', 20G', and 20H' can determine the power signal frequency from the first impedance difference described above. Despite small variations in their impedances, all of the controllers 22 of transmitter modules 20D', 20E', 20G', and 20H' select the same discrete frequencies from those allowed in the band for the power signals of their respective oscillators 26A and power amplifiers 26B.

[0322] In one embodiment, to ensure that resonators 30D', 30E', ​​30G', and 30H' all have not only the same power signal frequency but also the same phase, the following procedure is adopted and programmed into the software of each controller 22 of transmitter modules 20A'-201'. Statistically, a first independent controller 22 of transmitter modules 20D', 20E', 20G', and 20H' first turns on its corresponding oscillator 26A and power amplifier 26B to supply power to the resonant receiver subsystem 14 through its transmitter resonator. A second independent controller 22 of the other independent controllers 22 of transmitter modules 20D', 20E', 20G', and 20H' measures the input impedance of its corresponding transmitter resonator and detects, via its corresponding load detector 24A, small secondary changes in that impedance due to the first transmitter resonator's function. In effect, the second controller 22 sees a reflection of the first transmitter resonator's impedance through its interaction with the resonant receiver subsystem 14. The second controller 22 is programmed to conclude, based on the second impedance change, that another controller initially turned on its oscillator 26A and power amplifier 26B. After making this inference, the second controller 22 then turns on its oscillator 26A and power amplifier 26B and varies the phase of the power signal while measuring the power transmitted by its corresponding transmitter resonator using its transmitter power sensor 24B. The second controller 22 then varies the phase of the oscillator to search for the phase at which maximum power transfer occurs and sets the oscillator phase to that value. The oscillator phase thus determined ensures that the phase of the power signal transmitted by the second transmitter resonator is equal to the phase of the power signal transmitted by the first transmitter resonator to the resonant receiver subsystem 14; in one embodiment, the oscillator phase setting is based on substantially maximizing power transfer rather than absolutely equalizing the power signal phases.

[0323] In another embodiment, again based on transmitter resonators 30D', 30E', ​​30G', and 30H' being overlapped by the resonating receiver subsystem 14, detection of the proximity of the resonating receiver subsystem 14 is based on the test signal power drawn through the transmitter resonators 30D', 30E', ​​30G', and 30H'. In this embodiment, a low amplitude power signal is first maintained by the oscillators and power amplifiers corresponding to all transmitter resonators 30A'-301'. The controllers 22 of all transmitter modules 20A'-201' then sense the power drawn by their corresponding transmitter resonators 30A' using their corresponding transmitter power sensors 24B. Using their corresponding transmitter power sensors 24B, the controllers 22 of transmitter modules 20D', 20E', 20G', and 20H' sense the power being drawn through their corresponding transmitter resonators 30D', 30E', ​​30G', and 30H'. Based on detection of the drawn test signal power, the controllers 22 of transmitter modules 20D', 20E', 20G', and 20H' turn on full power in their corresponding power amplifiers 26B. The term first test signal power consumption is used herein to describe this power drawn from the test signal through the transmit resonators 30D', 30E', ​​30G', and 30H'. The test power signals of the power amplifiers 26B of transmitter modules 30A', 30B', 30C', 30F', and 30T that are not overlapped by the resonant receiver subsystem 14 may be turned off after an appropriate test period.

[0324] Equivalent to the impedance-based embodiment described above, the controllers 22 of transmitter modules 20D', 20E', 20G' and 20H' may require a threshold power consumption to disengage the resonant receiver subsystems 14 that reside in proximity to their corresponding transmitter resonators 30D', 30E', ​​30G' and 30H'.

[0325] In one embodiment, to ensure that the controllers 22 of the overlapping transmitter resonators 30D', 30E', ​​30G', and 30H' all set their corresponding oscillators 26A to the same frequency, the controllers 22 of the transmitter modules 20A'-20T are all provided with the same table of selected frequencies within any given tolerance band, e.g., the ISM band. Within that ISM band, several discrete frequencies are selected for inclusion in the frequency table. Thus, the number of tabulated frequencies within that ISM band is finite and limited, and the tabulated frequencies are spaced far enough apart that the various controllers 22 of the transmitter modules 20D', 20E', 20G', and 20H' can determine the power signal frequency from the first test signal power consumption described above. Despite small variations in their power consumption values, the controllers 22 of all of the transmitter modules 20D', 20E', 20G', and 20H' select the same discrete frequencies from among those allowed within the band for the power signals of their respective oscillators 26A and power amplifiers 26B.

[0326] In one embodiment, to ensure that resonators 30D', 30E', ​​30G', and 30H' all have not only the same power signal frequency but also the same phase, the following procedure is adopted and programmed into the software of each controller 22 of transmitter modules 20A'-201'. Statistically, a first independent controller 22 of transmitter modules 20D', 20E', 20G', and 20H' first turns on its corresponding oscillator 26A and power amplifier 26B to provide power to the resonant receiver subsystem 14 via its transmitter resonator. A second independent controller 22 of the other independent controllers 22 of transmitter modules 20D', 20E', 20G', and 20H' measures the power consumption of its corresponding transmitter resonator and detects, via its corresponding transmitter power sensor 24B, small quadratic variations in that power consumption that are a function of the first transmitter resonator. In effect, the second controller 22 sees a reflection of the impedance of the first transmitter resonator through its interaction with the resonant receiver subsystem 14. Based on the secondary change in power consumption, the second controller 22 is programmed to conclude that another controller initially turned on its oscillator 26A and power amplifier 26B. After making this inference, the second controller 22 then turns on its oscillator 26A and power amplifier 26B and varies the phase of the power signal while measuring the power transmitted by its corresponding transmitter resonator using its transmitter power sensor 24B. The second controller 22 then searches for the phase at which maximum power transmission occurs and sets the oscillator to that phase. The oscillator phase thus set ensures that the phase of the power signal transmitted by the second transmitter resonator to the resonant receiver subsystem 14 is equal to the phase of the power signal transmitted by the first transmitter resonator to the resonant receiver subsystem 14.

[0327] In one embodiment, when two different resonant receiver subsystems are adjacent to a multi-transmitter subsystem 12' and overlap with a different one or combination of transmitter resonators 30A'-30T, the two different transmitter resonators, or two different groups of transmitter resonators overlapped by the two resonant receiver systems, should not, and there is no requirement for them to, operate at the same frequency or phase. The ground shield grid 33' ensures this multidirectional independence by isolating all individual transmitter resonators 30A'-30T from each other. However, transmitter resonators overlapped by one particular resonant receiver subsystem must have their corresponding power signal amplifiers actively synchronized by their controllers, as explained above. This may result in two different transmitter resonators, or two different groups of resonators, operating at two specific lock-in frequencies within a band, with all signals within a particular group being in phase with each other.

[0328] In the above, two transmitter resonators transferring power to the same receiver resonator may be programmed to operate in such a way that the two transmitter resonators have in-phase power signals, thereby ensuring maximum power transfer. A different situation arises when two adjacent transmitter resonators, e.g., 30A' and 30B' in FIG. 14, are transmitting to two substantially similar corresponding receiver subsystems 14A and 14B. Both transmitter resonators 30A' and 30B' have fringe electric fields, with field lines extending, for example, from transmitter resonator 30A' to receiver subsystem 14B' and from transmitter resonator 30B' to receiver subsystem 14A. For example, a specific physical structure within system 10' is not common to ensure that the fields of transmitter resonator 30A' interact with the receiver resonators of receiver subsystem 14B.

[0329] In one embodiment, when both transmitter resonators 30A' and 30B' serve the same large receiver resonator that overlaps both transmitter resonators 30A' and 30B' (as in FIG. 13A), fringing fields are essentially not a problem because both transmitter resonators 30A' and 30B' are running the same frequency power signals with the same phase. For the situation shown in FIG. 14, the requirement is to ensure that any fringing fields of a given transmitter resonator are not allowed to be parasitic from transmitter resonator 30A', interacting with a receiver subsystem (e.g., 14B, which is intended to accept power from adjacent transmitter resonator 30B'). One way to achieve this goal is to drive the two adjacent transmitter resonators 30A' and 30B' 180 degrees out of phase with each other, so that the overlapping fringing fields from transmitter resonators 30A' and 30B' largely cancel each other out.

[0330] Because either of transmitter resonators 30A' and 30B' experiences the other of transmitter resonators 30A' and 30B' as a parasitic when their power signals are not 180 degrees out of phase, controller 22 for each of transmitter resonators 30A' and 30B' may increment the phase of the signal from its respective oscillator while measuring the power transmitted by the corresponding transmitter resonator 30A', 30B' using corresponding transmitter power sensor 24B. Controller 22 may then search for an adjusted oscillator phase that provides maximum transmit power through the corresponding transmitter resonator 30A', 30B' and then set the oscillator phase to that corresponding phase.

[0331] As explained above, the frequency and phase alignment for each resonant receiver system ensures that both resonant receiver systems receive maximum transferred power. In a typical embodiment, there may be multiple transmitter resonators, with several different resonant receiver subsystems receiving power, each receiving power from its own corresponding individual group of transmitter resonators at a frequency and phase selected by a controller corresponding to the transmitter resonators in the group. Adjacent transmitter resonators transferring power to different receiver subsystems may be 180° out of phase as a result of maximizing power transfer for each of the adjacent transmitter resonators. The process of maximizing power transfer adjusts oscillator phase. Because the impedances of the various transmitter modules are complex with slight variations in resistance, inductance, and capacitance, when the power signals in the transmitter resonators are actually equal (or differ by exactly 180°), the phase angles of the different oscillators at the maximum power transfer point may not be quite equal (or differ by exactly 180°).

[0332] To the extent that system 10′ comprises one circuit with an air gap between the primary and secondary sides, any power transfer measured or maximized in the transmitter resonator, e.g., at point 24E in FIG. 6 based on measurements by transmitter power sensor 24B, may only be measured or maximized in the secondary circuit, e.g., at point 44C in FIG. 7 based on measurements by receiver power sensor 44A. The measurements may be provided by transmitter power sensor 24B to controller 42 of receiver module 40, which may then communicate the measurements to controller 22 of transmitter module 20 by one of the means already described above.

[0333] The concept of a multi-transmitter near-field resonant wireless power transfer system is described above with reference to a system 10′ configured for simultaneous capacitive and inductive power transfer according to an adjustable transfer mode ratio at a variable resonant power signal oscillation frequency. In more general embodiments, the multi-transmitter near-field resonant wireless power transfer system need not be specifically a bimodal system, but can be a purely capacitive or purely inductive power transfer system.

[0334] In a further aspect, illustrated in the flowchart of FIG. 15, a wireless near-field method for transferring power at a variable resonant power signal oscillation frequency from a multi-transmitter subsystem 12′ to a single-resonant receiver subsystem 14 comprises: providing a multi-transmitter subsystem 12′ comprising a plurality of mutually independent transmitter resonators 30A′-301′, each driven by a corresponding transmitter module 20A′-201′, each independently configurable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, all of the transmitter resonators 30A′-301′ having a common transmit plane; and a common transmit plane comprising a single receiver resonator 50 overlapping two or more of the transmitter resonators (30D′, 30E′, 30G′, and 30H in FIG. 13A ) positioned adjacent to the resonant receiver subsystem 14. Measuring the input impedance of each of the transmitter resonators 30A'-301' and setting the power signal to each of the plurality of mutually independent transmitter resonators 30A'-301' to one of an off state and an active state based on the corresponding measured resonator input impedance.

[0335] The method may further include selecting a power signal oscillation frequency for the corresponding transmitter resonator (30D', 30E', ​​30G', and 30H' in FIG. 13A) from among a plurality of preset power signal oscillation frequencies based on a measured input impedance of the corresponding transmitter resonator (resonators 30D', 30E', ​​30G', and 30H in FIG. 13A).

[0336] The method may further include setting a power signal of each active transmitter resonator (30D', 30E', ​​30G', and 30H') to a corresponding selected frequency.

[0337] The method may further include adjusting the phase of the power signal applied to each corresponding transmit resonator (resonators 30D', 30E', ​​30G', and 30H in FIG. 13A) to a phase that substantially maximizes power transfer through the transmitter resonator (30D', 30E', ​​30G', and 30H' in FIG. 13A).

[0338] In a further aspect, illustrated in the flowchart of FIG. 16, a wireless near-field method for transferring power at a variable resonant power signal oscillation frequency from a multi-transmitter subsystem 12′ to a single-resonant receiver subsystem 14 comprises: providing a multi-transmitter subsystem 12′ comprising a plurality of mutually independent transmitter resonators 30A′-30F, each driven by a corresponding transmitter module 20A′-20F, each independently configurable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, all of the transmitter resonators 30A′-30F having a common transmit plane; and a common transmit plane comprising a single receiver resonator 50 overlapping two or more of the transmitter resonators (30D′, 30E′, 30G′, and 30H′ in FIG. 13A ) positioned adjacent to the resonant receiver subsystem 14. This includes measuring the power drawn by each of the transmitter resonators 30A'-30F from the test signal, and setting the power signal to each of the plurality of mutually independent transmitter resonators 30A'-30F to one of an off state and an active state based on the corresponding measured resonator test power consumption.

[0339] The method may further include selecting a power signal oscillation frequency for the corresponding transmitter resonators (30D', 30E', ​​30G', and 30H in FIG. 13A) from among a plurality of preset power signal oscillation frequencies based on a measured test power drawn by each of the corresponding transmitter resonators (resonators 30D', 30E', ​​30G', and 30H in FIG. 13A).

[0340] The method may further include setting the power signal of each active transmitter resonator (30D', 30E', ​​30G', and 30H in FIG. 13A) to a corresponding selected frequency.

[0341] The method may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator (30D', 30E', ​​30G', and 30H in FIG. 13A) to a phase at which power transfer through the transmitter resonator (30D', 30E', ​​30G', and 30H in FIG. 13A) is substantially maximum.

[0342] In a further aspect, shown in the flowchart of Figure 17, a wireless near-field method for transferring power at a variable resonant power signal oscillation frequency from a multi-transmitter subsystem 12' to two or more receiver subsystems 14A, 14B (Figure 14) includes the steps of: providing a multi-transmitter subsystem 12' comprising a plurality of mutually independent transmitter resonators 30A'-30F (in Figure 14), each of the transmitter resonators driven by a corresponding transmitter module 20A'-20F (see Figure 13B), each transmitter module 20A'-20F independently configurable to one of a plurality of preset power signal oscillation frequencies in a predetermined frequency band, and all transmitter resonators 30A'-30F having a common transmitting surface. two or more resonant receiver subsystems 14A adjacent to a common transmission plane, measuring the input impedance of each transmitter resonator 30A', 30B', and setting the power signal to each of the plurality of mutually independent transmitter resonators 30A'-30F to one of an off state and an active state based on the corresponding measured resonator input impedance;

[0343] The method may further include selecting a power signal oscillation frequency for the corresponding transmitter resonator 30A', 30B' from among a plurality of preset power signal oscillation frequencies based on the measured input impedance of each of the active transmitter resonators (resonators 30A', 30B' in FIG. 14).

[0344] The method may further include setting the power signal of each active transmitter resonator 30A', 30B' to a corresponding selected frequency.

[0345] The method may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator 30A', 30B' to a phase that substantially maximizes power transfer through the transmitter resonator 30A', 30B' (FIG. 14).

[0346] In a further embodiment, illustrated in the flow chart of FIG. 18, a wireless near-field method is shown.

[1400] is for transmitting power at a variable resonant power signal oscillation frequency. A multi-transmit subsystem 12' to two or more receiver subsystems 14A, 14B (of FIG. 14) includes:

[1410] Providing a multi-transmitter subsystem 12' with a plurality of mutually independent transmit resonators 30A'-301' (FIG. 14), each of the transmitter resonators being driven by a corresponding transmitter module 20A'-20F (see FIG. 13B), each transmitter module 20A'-20F being independently settable to one of a plurality of preset power signal oscillation frequencies in a predetermined frequency band, and all of the transmit resonators 30A'-30F having a common transmit surface. arranging two or more resonant receiver subsystems 14A, 14B adjacent to a common transmission plane (transmitter resonators 30A', 30B' of FIG. 13); measuring the power drawn by each of the transmitter resonators 30A'-30F from a test signal; and setting a power signal to each of the plurality of mutually independent transmitter resonators 30A'-30F to one of an off state and an active state based on the corresponding measured resonator test power consumption.

[0347] The method may further include selecting a power signal oscillation frequency for the corresponding transmitter resonator 30A′, 30B′ from among a plurality of preset power signal oscillation frequencies based on the measured input impedance of each of the active transmit resonators (resonators 30A′, 30B′ in FIG. 14 ).

[0348] The method may further include setting the power signal of each active transmit resonator 30A', 30B' to a corresponding selected frequency.

[0349] The method may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator 30A', 30B' to a phase that substantially maximizes power transfer through the transmitter resonator 30A', 30B' (FIG. 14).

[0350] 20A and 20B, 21A and 21B, and 22A and 22B, and based on the systems of FIGS. 1-10 and 12-14, a near-field resonant wireless power transfer system 10" is presented in accordance with the schematic diagram of FIG. 19A for wirelessly transferring power from a photovoltaic solar cell 420 to a power load 70. A highlight numbering system is used in the labels on FIG. 19A so that the parallels with FIGS. 19A and 13B are apparent, and thereby also with FIGS. 6 and 7. By this numbering scheme, DC power is supplied from the solar cell 420 to the transmitter module 20 via a power conditioning unit (PCU) 430, which beyond converts the DC voltage and DC current to levels that can be further transmitted by the power amplifier 26B, also provides appropriately regulated levels of voltage and current to drive the remainder of the system components, including the small signal electronic components within the transmitter module 20. The PCU 430 represents an adaptively changing load to solar cell 420 to accommodate the fluctuating power provided by solar cell 420 and the fluctuating output impedance presented by solar cell 420 to PCU 430, thereby allowing PCU 430 to always absorb power from solar cell 420 at the maximum possible rate despite fluctuations in power from solar cell 420.

[0351] Oscillator 26A may be used to modulate power amplifier 26B" at a frequency suitable for wireless power transfer, as already explained above. Power amplifier 26B may be of the same design as amplifier 26B shown in FIG. 8, supplied with DC power from PCU 430 instead of DC voltage 127E. In an alternative embodiment, power amplifier 26B" may be suitably provided with circuitry to maintain its own oscillation, thereby eliminating oscillator 26A, as is well known in the art of wireless systems.

[0352] 19A, all of the components of transmitter module 20 are under the control of controller 22, as are the corresponding components of transmitter module 20 of FIG. 6, which can transfer power to "transmit resonator 30" via "transmit tuning network 28" under the control of controller 22; for clarity, not all of the components of transmitter module 20 are shown in FIG. 19A. Sensors and detectors 24A, 24B, 24C, and 24D of FIG. 6 may be present within transmitter module 20 and connected to controller 22, and may perform the same functions as already described with reference to FIG. 6.

[0353] Power may be transferred wirelessly from the transmitter module 20" to the receiver module 40" via the transmit resonator 30" and the receiver resonator 50". From the receiver module 40", power may then be transferred to a DC load 70". The transmission of power between the transmit resonator 30" and the receiver resonator 50" may be by near-field wireless transfer as follows: As explained above with reference to FIGS. 6-10, near-field wireless power transfer according to FIG. 19A is not limited to being bimodal, but can be purely capacitive or purely inductive.

[0354] Receiver module 40" may have the same components as receiver 40 of FIG. 7, and for clarity, a reduced set of those components is shown in FIG. 19A. Sensor 44A and detector 44B of FIG. 7 are not shown in equivalent form in FIG. 19A, but may be present. Receiver tuning network 48" of FIG. 19A may be an integration of compensation network 46A, matching network 46B, rectifier 46D, and filter 46C. Power may be transferred from receiver tuning network 28" to load manager 46E", both of which may be under the control of receiver controller 42.

[0355] With respect to rectifier 46D, shown in more detail in FIG. 7, the input impedance of this device depends directly on the load seen by the output of the device.

[0356] In operation, the near field resonant wireless power transfer system 10" may function in the same manner as the near field resonant wireless power transfer system 10 of FIG. 1, with FIGS. 6-10 showing that the applied voltage VDD on each power amplifier 26B is replaced by a power signal from a power conditioning unit (PCU) 430, which receives its power from an associated power source, which in this embodiment is a solar cell 420.

[0357] In another embodiment, power conditioning unit 430 may be omitted from the system shown in FIG. 19A and power transfer system 10, instead of being configured or operated to also function as a power conditioning system. This may be accomplished, for example, by configuring controller 22″ to adjust the input DC equivalent resistance of power amplifier 26B based on the power level measured by power sensor 24B of FIG. 6, where the term “input DC equivalent resistance” is used herein to describe the ratio of DC voltage to DC current at the DC terminals of power amplifier 26B. Controller 22 makes adjustments based on the power measurements, with the expectation that a maximum power point of transferred power will be achieved when the input impedance of power amplifier 26B matches the output impedance of solar cell 420. In this embodiment, system 10″ functions as what is known in the industry as a maximum power point tracker, ensuring that power is always transferred at a rate more suitable for the power consuming load than would be obtained if the delivery of power were unregulated. In another embodiment, controller 22″ may be configured to measure the output impedance of the power source, which in this embodiment is solar cell 420, and then adjust the input impedance of power amplifier 26B based on the measured output impedance of solar cell 420.

[0358] In addition to adjusting the input impedance of power amplifier 26B, controller 22 may also adjust one or more of the settings of transmitter tuning network 28 and the frequency of oscillator 26A. Additionally, transmitter controller 22" can make the adjustments already described above based on measurements by load detector 24A, shown in FIG. 6, which provides more detail on transmitter module 20 and its circuitry. Load detector 24A senses the effect of load 70 at point 24E in FIG. 6.

[0359] The receiver controller 42" may also adjust one or more of the settings of the receiver tuning network 48" and the load management system 46E" to improve the efficiency of power transfer based on measurements by the receiver power sensor 44A and the load detector 44B (both shown in FIG. 7).

[0360] Given the power conditioning capabilities of system 10, it will be appreciated that there is no a priori reason why the system's power transfer function should be limited to short-range wireless transmission over an air gap, as in FIG. 19A. Accordingly, in another embodiment, a power conditioning unit 410 is shown in FIG. 19B based on the elements of system 10 of FIG. 19A. The transmitter tuning network 28″ is in direct electrical communication with the receiver tuning network 48 through a suitable non-air-gap connection 60″. This communication is via a high-frequency power signal, which constitutes the power being transferred by and to the system. Appropriate reactive electronic components may be employed in well-known configurations to isolate any DC voltage and current levels in the transmitter module 20 from such levels in the receiver module 40. The transmitter resonator 30″ and receiver resonator 50″ are absent in this embodiment and are avoided by the direct communication connection between the transmitter tuning network 28″ and the receiver tuning network 48″.

[0361] The function of the power transfer system of Figures 19A and 19B as a power conditioning system can be better appreciated by considering Figure 19B, where the absence of transmitter resonator 30 and receiver resonator 50 simplifies power conditioning. These apply equally to those resonators present (as in FIG. 19A). The systems of FIGS. 19A and 19B have four independent control parameters that can be adjusted to the load 70" during operation to regulate the power being transferred to the receiver module 40. Typical commercial power conditioning units are commonly known as boost converters, by increasing the output voltage above that of the source voltage. These devices only have two control parameters.

[0362] The first independent control parameter that may be adjusted during operation to adjust the power being transferred to receiver module 40, and thereby load 70, is the oscillation frequency of power amplifier 26B, which is adjustable by controller 22A within oscillator 26A.

[0363] A second independent control parameter, thereby load 70, that may be adjusted during operation to regulate the power being transferred to receiver module 40 is the output load on rectifier 46D of receiver module 40. That output load, in turn, directly determines the input impedance of rectifier 46D and the input impedance of receiver module 40. This, in turn, is the load seen by transmitter module 20, which directly determines the input DC equivalent resistance of power amplifier 26B. Manipulation of the output load on rectifier 46D is accomplished through load management system 46E of receiver module 40 (see FIG. 19A), which is under the control of receiver controller 42. This second independent control parameter, while characteristic of the receiver module, naturally controls the load seen by the power supply. The control point for manipulating this parameter is load management system 46E of receiver module 40.

[0364] The third and fourth independent control parameters that can be adjusted during operation to regulate the power being transferred to the receiver module 40, and thereby the load 70, are the characteristics of the rectifier 46D (see FIG. 7) and the power amplifier 26B (see FIG. 19A) of the receiver module 40, which are similar in nature but completely independent of each other. Both the rectifier 46D and the power amplifier 26B comprise multi-terminal amplifying devices and rely on modulation of the passage of current between two terminals through the multi-terminal device by a voltage signal applied to the third terminal of each device. The simplest multi-terminal amplifying device that can be used in each of the rectifier 46D and power amplifier 26B is a transistor. This allows for a phase difference to exist between the voltage signal and the current signal generated by or in the device. That voltage-current phase difference is adjustable via an applied voltage. The rectifier 46D can be an adjustable-phase radio frequency rectifier, whose voltage-current phase difference can be adjusted via the receiver controller 42. In the case of the power amplifier 26B, the voltage-current phase difference can be adjusted via the transmitter controller 22. Rectifier 46D may usefully comprise a differential self-synchronous radio frequency rectifier.Rectifier 46D may comprise a differential switch mode self-synchronous radio frequency rectifier.

[0365] While the examples of FIGS. 19A and 19B are based on the transfer of power from solar cells, or by extension from a solar array, the power delivered by the solar cells 420 can vary significantly down to zero depending on the sunlight. Many other power sources exist that suffer from variable outputs, both in terms of power and the voltage generated. Among these are generating turbines, wind turbines, and various batteries and accumulators. Wind turbines can vary significantly in the generation of power, and various batteries can have a wide range of power depletion curves. Given the efficiency of the power transfer in either of these systems 10″ and 410, for example and without limitation, they may be configured to receive power from a utility battery with a slow open-circuit voltage decay curve. As discussed above, the load management system 46E″ may be configured to modify the input DC equivalent resistance of the power amplifier 26B, and the controllers 22″ and 42″ may be configured to render the required voltage level to the load 70 until such voltage is no longer maintained by the power transfer and adjustability of the parameters of the systems 10 and 410.

[0366] FIG. 19A and its associated descriptive text address the near-field wireless transmission of power from a single solar cell 420 to a single load 70, typically a battery. In practical implementations of larger solar cell power systems, an array of cells is typically used, such that a power transfer scheme similar to that described with reference to FIGS. 12, 13A, and 13B may be employed, with multiple transmitter subsystems, typically a single receiver subsystem. This situation is illustrated in FIGS. 20A and 20B, which are exploded front and back views, respectively, of a solar panel 400 having a transparent solar cover 440 with one near-field wireless power transmission subsystem per solar cell 420, thereby providing, by way of example, 60 near-field wireless power transmission subsystems 16, each transmission subsystem 16 comprising a transmitter resonator 30″, a transmitter module 20″, and power. Coordination unit 430, as described with reference to Figure 19A. To avoid confusion, transmission subsystem 16 is not labeled in Figure 19A, but is shown and labeled in Figures 20B, 21B, and 22B, as described further below.

[0367] In one embodiment, coupling individual solar cells of a solar panel composed of multiple solar cells to a power transmission and management system enables cell-level power management. By providing power management for each individual cell, power collection can be optimized for each cell, resulting in increased efficiency for the entire solar panel system. In such an embodiment, the impact of individual cell failure or poor connections between cells is mitigated. Power collection at the individual cell level enables maximum power harvesting even in less than ideal conditions, such as when rain, shade, or debris covers a portion of the solar panel.

[0368] To avoid clutter, only one short-range wireless power transmission subsystem 16 is labeled in Figure 20B. In Figures 20A and 20B, the transmitter resonator 30 of each transmitting subsystem 16 may be located behind its corresponding solar cell 420. The flat area of ​​the solar cell when viewed from the front of the panel in Figure 20A represents the active solar radiation receiving and energy converting semiconductor device itself and is correspondingly labeled 420, while the flat area of ​​the device when viewed from the back in Figure 20B represents the transmitter resonator and is correspondingly labeled 30. The transmitter resonator 30" can have a surface area that can be at least a majority of the extent of the active solar radiation receiving surface of each short-range wireless power transmission subsystem 16, and the power conditioning units 430 of each short-range wireless power transmission subsystem 16 are integrated with each other in FIG. 20B and labeled 450; the integrated components 450 are not labeled in FIG. 19A but are shown as a unit and labeled in FIGS. 20B, 21B, and 22B, as described further below. A single receiver resonator 50" can be attached to a frame 460 of the solar panel 400, and a single receiver module 40" can be attached directly to the rear of the receiver resonator 50.

[0369] In operation, the near field resonant wireless power transfer system 10" may function in the same manner as the near field resonant wireless power transfer system 10' of Figures 12, 13A, and 13B, with the applied voltage V DD on all of the power amplifiers 26B being replaced by a power signal from a power conditioning unit (PCU) 430, which receives its power from an associated solar cell 420.

[0370] In another embodiment of the system of Figures 20A and 20B, the frame 460 may be configured to be a suitable receiver resonator for receiving power from all transmitter resonators 30" and receiver modules 40", and in this embodiment, the plates in the frame are not resonators but may be simple flat sheets of non-conductive material.

[0371] In another implementation, a solar panel 400′, shown in front and rear views in FIGS. 21A and 21B, respectively, has each near-field wireless power transmission subsystem transfer power to one near-field wireless power receiver subsystem. Although the frame 460 is shown as being filled by an opaque plate 470, the plate 470 need not be part of either the near-field electric or magnetic circuit. For clarity, the same components are numbered on the transmitting side as in FIGS. 20A and 20B. On the receiving side, the numbering of FIG. 19A is adopted. Again, to avoid clutter, only one receiving device is labeled.

[0372] In operation, the solar panel configuration 400' of FIGS. 21A and 21B may have the individual transmitter modules 20 linked by hardwires (not shown) so that they may be in phase, thereby allowing for at least power loss in transmission. In other embodiments, the transmitter modules 20' may function independently, as described above with reference to FIGS. 14, 17, and 18.

[0373] In a further implementation, shown as "solar panel configuration 400" in the front and rear views of FIGS. 22A and 22B, respectively, an array of, for example, 25 solar cells is shown arranged in five rows of five cells 420 each. Each solar cell 420 has a transmitter resonator 30" behind it and a unit 450 comprising its corresponding transmitter module 20" and power conditioning unit 430. At the bottom and top of the array, and between each two rows of solar cells, are arranged in a plane substantially perpendicular to the plane of the solar cells 420, and each receiver resonator 50" is in wired electrical communication with its corresponding receiver module 40". As with the previous solar panel embodiment, an example of each component is labeled. As with the implementations shown in FIGS. 20A and 20B and 21A and 21B, in some embodiments, the solar panel configuration 400" may also have a frame 460, which is not shown in FIGS. 22A and 22B for clarity.

[0374] In operation, the transmitter resonators 30 of the solar cells 420 in a row of the system 400 transmit power to both the receiver resonators 50 above and below. However, in this embodiment, additional features of the various nearest-neighbor receiver resonators 50 are resonantly coupled to share the collected power among themselves. Thus, the collected power collected by all receiver resonators 50 in the array may be tapped through any one or more of the various receiver modules 40. In some embodiments, the power collected by all receiver modules 40 may be tapped through only the bottom receiver module 40, as an example. Any one of the receiver modules 40 on any resonator 50 may function as a receiver module to collect the power of the row of solar cells 420, while also functioning as a transmitter module to transmit the power collected through its associated resonator 50 to another resonator 50 in its vicinity. This action may be repeated down the array to transfer power to the bottom receiver module 40.

[0375] In another embodiment of the system of Figures 22A and 22B, a frame surrounding the planar periphery of the solar array of Figures 22A and 22B, similar to frame 460 of Figures 20A and 20B, may be a receiver resonator-bearing receiver module 40 and may receive power from the various resonators 50. In this manner, the total power generated by all solar cells 420 in the array may be received by the resonator frame 460 and tapped for further electrical transmission via the receiver module 40.

[0376] Power collection at the individual solar cell level can be achieved using wired connections, but using wireless transmission methods for solar panels can reduce wiring and therefore manufacturing costs.

[0377] In a further aspect described with reference to the flowchart of FIG. 23 , a method is provided for transferring power from a solar cell 420 to a power load 70, the method including converting power from the solar cell 420 into an oscillating power signal having an oscillation frequency at a transmitter module 20; transferring the power to a transmitter resonator 30 in wired electrical communication with the transmitter module 20 and configured to resonate at the oscillation frequency; receiving the power in a receiver resonator 50 configured to resonate at the oscillation frequency and configured to receive power from the transmitter resonator 30 via at least one of capacitive coupling and magnetic induction; and receiving the power in a receiver module 40 in wired electrical communication. Rendering the power load 70 "received power" via wired electrical communication using the receiving resonator 50 to the power load 70

[1550] . The method may further include converting the voltage and current of the power from the solar cell 420 to a voltage and current adapted to the transmitting module 20 before converting the power to an oscillating power signal.

[0378] In a further embodiment of the method described with reference to the flowcharts of FIGS. 19A and 24, a method for transferring power from an array 400 of solar cells 420 to a power load 70 is provided, the method including converting power from each of the solar cells 420 in the array 400 into an oscillating power signal having an oscillation frequency; transferring the power to a corresponding transmitter resonator 30 from among a second plurality of transmitter resonators 30 configured to resonate at the oscillation frequency; receiving the power in a receiver resonator 50 configured to resonate at the oscillation frequency and positioned to receive power from the plurality of transmitter resonators 30 via at least one of capacitive coupling and magnetic induction; receiving the power in a receiver module 40 in wired electrical communication with the receiver resonator 50; and rendering the received power in DC form via the wired electrical communication to a power load 70. The method may further include converting the voltage and current of the power from each solar cell 420 to a voltage and current adapted to the corresponding transmitter module 20 before converting the power into the oscillating power signal. Receiving power in the receiver resonator 50 may include receiving power at receiver resonators positioned around the planar periphery of the array 400 of photovoltaic cells.

[0379] In a further embodiment of the method described with reference to the flowcharts of Figures 19A and 25, a method is provided for transferring power from an array 400' of solar cells 420 to a power load 70, the method including converting, in each of a first plurality of corresponding transmitting modules 20, power from each of the solar cells 420 in the array 400' into an oscillating power signal having an oscillating frequency. transferring power to a corresponding transmitter resonator 30 from among a second plurality of transmitter resonators 30, each transmitter resonator 30 configured to resonate at the oscillation frequency; and receiving power from each transmitter resonator 30 in a corresponding receiver resonator 50 configured to resonate at the oscillation frequency, wherein each receiver resonator 50 is further configured and arranged to receive power from the transmitter resonator 30 via at least one of capacitive coupling and magnetic induction, receiving power from each receiver resonator 50 in a corresponding receiver module 40 in wired electrical communication with the receiver resonator 50, and rendering the power in DC form via wired electrical communication to a power load 70. The method may further include converting the voltage and current of the power from each photovoltaic cell 420 to a voltage and current adapted to the corresponding transmitter module 20 before converting the power to the oscillating power signal.

[0380] In a further embodiment described with reference to the flowcharts of Figures 19A and 26, a method is provided for transferring power from an array 400" of solar cells 420" to a power load 70" (in Figure 19A), the method including converting, in each of a first plurality of corresponding transmitting modules 20, "power from each of the photovoltaic cells 420 in the array 400" into an oscillating power signal having an oscillating frequency. each transmitter resonator 30″ is configured to resonate at an oscillation frequency and receives power from a “respective transmitter resonator 30″ in any nearby receiver resonator 50 of the third plurality of receiver resonators 50″ configured to resonate at the oscillation frequency, and each receiver resonator 50″ is further configured and arranged to receive power from the transmitter resonator 30 via at least one of capacitive coupling and magnetic induction, share the received power among the third plurality of receiver resonators 50, and render via wired electrical communication to a power load 70 “receive power” in DC form from one or more of the third plurality of receiver resonators 50 via a corresponding one or more receiver modules 40. The method may further include converting the voltage and current of the power from each photovoltaic cell 420 to a voltage and current adapted to a corresponding transmitter module 20 before converting the power into an oscillating power signal.

[0381] FIG. 27A shows a representative portion 500 of an extended near-field wireless power distribution system in an electric vehicle having a conductive chassis 510. In this embodiment of the general system 10 of FIG. 19A, power. The power source is a rechargeable battery 520 rather than a solar cell 420, and the load 70" is an electric motor 530 rather than a battery as in FIG. 19A. The system shown in FIG. 14A may optionally include a power conditioning unit 430 as in FIG. 19A in other embodiments, and the transmitter modules may cooperate to provide power conditioning as described above with reference to FIG. 19B.

[0382] The system shown in FIG. 27A and described in more detail below may operate by capacitive, inductive, or bimodal power transfer. Referring to FIGS. 4B and 19A, the transmitter resonator 30″ comprises a dielectric element 138 sandwiched between conductive antennas 132 and 134, and referring to FIGS. 4B and 19A, the receiver resonator 50″ comprises a dielectric element 158 ​​sandwiched between conductive antennas 152 and 154. The transmitter module 20″ is attached directly to the antenna 132, which may also be electrically connected between the battery 520 and the transmitter resonator 30. The receiver module 40″ is shown attached directly to the electric motor 530, which may also be electrically connected between the receiver resonator 50″ and the motor 530.

[0383] FIG. 27B shows a representative portion 500′ of the general system 10 of FIG. 19A in which, in this embodiment of the general system 10″ of FIG. 19A, the power source is again a rechargeable battery 520 rather than a solar cell 420 as in FIG. 27A, and the load 70″ is an electric motor 530 rather than a battery as in FIG. 19A. The system shown in FIG. 27B can optionally include a power conditioning unit 430 as in FIG. 19A. In other embodiments, the transmitter module 20″ and the receiver module 40″ can work together to provide power conditioning, as described above with reference to FIG. 19B.

[0384] The system shown in Figure 27B and described in more detail below may operate by capacitive, inductive, or bimodal power transfer. With reference to Figures 4B and 19A, transmitter resonator 30" comprises a dielectric element 138 sandwiched between conductive antennas 132 and 134, and with reference to Figures 4B and 19A, receiver resonator 50" comprises a dielectric element 158 ​​and conductive antenna 152; antenna 154 of Figure 27A is absent from resonator 50" in this embodiment. The transmitter module 20" is shown mounted directly to the antenna 132, which also serves as a frame or holder for the battery 520. The transmitter module 20" may be electrically connected between the battery 520 and the transmitter resonator 30. The receiver module 40" is shown mounted directly to the electric motor 530; in this embodiment, the receiver module 40" may be electrically connected between the motor 530 and the chassis 510; in this configuration, there is sufficient coupling between the chassis 510 and the antenna 152 for suitably efficient power transfer. Electrically conductive mechanical components of the system, i.e., components having a load-bearing structural function within the system, may thereby form part of the resonant structure of the power transfer system.

[0385] In the embodiment shown in Figures 27A and 27B, the focus is specifically on the power supplied to the electric motor 530 that drives one of the vehicle's wheels, but an equivalent arrangement may be implemented for any electrical subsystem on a vehicle using multiple appropriately adapted receiver modules 40, all with power provided by the transmitter module 20.

[0386] The configurations of Figures 27A and 27B for power transfer to the vehicle's electrical subsystems of Figures 27A and 27B eliminate the need for complex automotive wiring harnesses at most hubs, which present difficulties during vehicle manufacturing and are a source of significant manufacturing costs. The embodiments of Figures 27A and 27B, along with their extension to other electrical subsystems of the vehicle, may be described as an extended near-field wireless power distribution system.

[0387] Beyond the other wheels of an electric vehicle, this configuration can extend to headlights and other vehicle accessories, including, but not limited to, interior lights, dashboard displays, gauges, digital electronics, navigation systems, warning systems, etc. Nor is it limited to electric vehicles. It may be applied to hybrid or internal combustion engines to distribute power as needed and as required. It can equally be applied to other vehicles using any electrical system that requires electrical power. Non-limiting examples include motorized and non-motorized bicycles, aircraft, boats, and other vehicles that employ on-board power sources. The battery or power source need not be limited to being mounted on the vehicle. The principles described with respect to Figures 1-11, 19A-19B, and 27A-27B also apply to stationary and vehicular systems that require electrical power. For example, but not limited to, a fixed rail for providing power to a moving vehicle, supplied from a stationary source.

[0388] 1 and 19A, the transmitter module 20" and the transmit resonator 30" are both integrated into the primary side 12, the transmitter module 20" and the transmit resonator 30" of FIG. 19A are both integrated into the primary side 12, the transmitter module 20" and the transmit resonator 30" of FIG. 19A are both integrated into the primary side 12, and the receiver module 40" of FIG. 19A may be integrated into the base of the monitor 610 itself. Referring to FIG. 4B, the antenna 152 forms the bottom of the base of the monitor 610 and is separated from the antenna 154 by a dielectric 158.

[0389] The housing and structural frame 630 of the monitor 610 may be at least partially conductive and may function as one continuous conductor (see FIG. 19A) for electrically supplying the power signal from the antenna 154 through the receiver module 40 to the circuitry of the monitor 610 representing the load resonator 70 of FIG. 19A. In other embodiments, the housing and structural frame 630 of the monitor 610 may be a non-conductive polymer, and a separate conductor extends from the antenna 154 to the circuitry of the monitor 610 representing the load resonator 70 of FIG. 19A.

[0390] As shown in another embodiment of a power supply system 600′ for powering a computer monitor 610 in FIG. 28B , the base of the monitor 610 can include only the antenna 152 and the dielectric 158; in this embodiment, a metallic conductive portion of the monitor housing or frame 630 acts as the antenna instead of the antenna 154, and the housing or frame 630 has sufficient coupling with the antenna 152 under the dielectric 158 to provide sufficiently efficient power transfer. The receiver module 40″ of FIG. 19A can be incorporated into the base of the monitor 610, or the receiver module 40 of FIG. 19A can be incorporated within the monitor 610 itself. The housing and structural frame 630 of the monitor 610 can act as one continuous electrical contiguous unit. A conductor for supplying a power signal via the receiver module 40 to the circuit of the monitor 610 representing the load resonator 70 of FIG. 19A.

[0391] System 600 may optionally include a power conditioning unit 430 as in FIG. 19A. In some embodiments, transmitter module 20" and receiver module 40" use near-field wireless power transfer but may function together to provide power conditioning as described with reference to FIG. 19A. The near-field wireless power transfer system of FIG. 28A eliminates the need for cumbersome power cables to supply power to monitor 610 and employs mechanical structural elements of the system as integral electrical / electronic components in the power transfer configuration.

[0392] As described with reference to the flowchart of FIG. 29 and the systems of FIGS. 19A and 19B, a method for transferring power from a DC power source 420 to a power load 70 is provided, the method comprising: a power transmission system 10″, 410 in wired electrical communication with the power source 420; and a power transmission system 10″, 410″ comprising an oscillator 26A capable of oscillating at an oscillation frequency; a power amplifier 26B″ and a transmitter tuning network 28″; and a receiver tuning network 48″ and a load management system 46E″ both under the control of a receiver controller 42″, the load management system 46E″ being in wired electrical communication with the power load 70 and converting power from the power source 420 at the power amplifier 26B into an oscillating power signal having an oscillation frequency; and transferring the power signal from the power amplifier 26B to the load management system 46E under the control of the transmitter controller 22 via the transmitter tuning network 28″ and the receiver tuning network 48. adjusting at least one of the oscillation frequency, the input DC equivalent resistance of the power amplifier 26B, the transmitter tuning network 28, the receiver tuning network 48, and the load management system 46E to change the rate of power transmission and rendering in DC form via wired electrical communication to the power load 70 "power received by the load management system 46E."

[0393] Transferring the power signal through the transmitter tuning network 28" and the receiver tuning network 48" may include transferring the power by wired or wireless communication. Transferring the power by wireless communication may include transferring. Power via near field communication. Transferring power via near field communication may include transferring power via at least one of capacitive coupling and inductive coupling. Transferring power from a DC power source 420 may include transferring power from at least one solar cell 420, and transferring power from a DC power source may include transferring power from at least one battery. Transferring power from a DC power source may include transferring power from a power source having a fluctuating voltage.

[0394] In another embodiment, with reference to the flowchart of FIG. 30 and taking a more in-depth look at the systems of FIGS. 19A and 19B, a method for transferring power from a DC power source 420 to a power load 70 is provided. The method includes: providing a power transmission system 10″, 410 in wired electrical communication with the power source 420, the power transmission system 10″, 410 comprising a radio frequency power amplifier 26B in radio frequency communication with an adjustable phase radio frequency rectifier 46D (see FIG. 7) in wired electrical contact with the power load 70; converting power from the DC power source 420 to a radio frequency oscillating power signal in the amplifier 26B; converting the radio frequency oscillating power signal to a DC power signal in the rectifier 46D; and adjusting the efficiency of the power transfer by adjusting the current-voltage phase characteristic of the rectifier 46D. Providing an adjustable phase radio frequency rectifier may include providing a differential self-synchronous radio frequency rectifier 46D.

[0395] The method may further include adjusting the efficiency of the power transfer by adjusting the DC equivalent input resistance of the amplifier 26B. Providing the power transfer system 10", 410 may include providing a load management system 46E in wired communication between the rectifier 46D and the load 70. Adjusting the DC equivalent input resistance of the amplifier 26B may include adjusting the input impedance of the rectifier 46D by adjusting the load management system 46E. Adjusting the load management system 46E may include automatically adjusting the load management system 46E.

[0396] The method may further include adjusting the efficiency of the power transfer by adjusting a current-voltage phase characteristic of the power amplifier 26B. Providing the power transfer system 10", 410 may include providing a transmitter controller 22" in communication with the power amplifier 26B" for controlling the power amplifier 26B". Adjusting the current-voltage phase characteristic of the power amplifier 26B may be performed by the transmitter controller 22. Adjusting the current-voltage phase characteristic of the power amplifier 26B may be performed automatically by the transmitter controller 22.

[0397] The method may further include adjusting the efficiency of the power transfer by changing the oscillation frequency of the power amplifier 26B.

[0398] Providing the power transfer system 10", 410 may include providing a receiver controller 42" in communication with the rectifier 46D for controlling the rectifier 46D. Adjusting the current-voltage phase characteristic of the rectifier 46D may be performed by the receiver controller 42. Adjusting the current-voltage phase characteristic of the rectifier 46D may be performed automatically by the receiver controller 42.

[0399] Providing the power transfer system 10", 410 may include providing the power amplifier 26B in direct wired radio frequency communication with the adjustable phase radio frequency rectifier 46D (via connection 60 of FIG. 19B). Providing the power transfer system 10", 410 may include providing the power amplifier 26B in wireless short-range radio frequency communication with the adjustable phase radio frequency rectifier 46D.

[0400] Providing the power transfer system 10", 410 may include providing the transmitter resonator 30 in wired radio frequency communication with the power amplifier 26B' ​​and the receiver resonator 50 in wired radio frequency communication with the radio frequency rectifier 46D. The method may further include operating the transmitter resonator 30" and the receiver resonator 50" in wireless near-field radio frequency communication. Providing the power transfer system 10", 410 may comprise providing the power amplifier 26B in at least one of capacitive near-field wireless and inductive near-field wireless radio frequency communication with the rectifier 46D. Providing the power transfer system 10", 410 may include providing the power amplifier 26B in bimodal wireless near-field communication with the rectifier 46D.

[0401] The method may further include providing a power conditioning unit 430 electrically disposed between the power source 420 and the power transmission system 10 and conditioning the power. The regulation unit 430 regulates at least one of the current and voltage from the power source 420 to improve the efficiency of the power transfer.

[0402] Considering the systems of FIGS. 19A and 19B more fully and with reference to FIG. 7, a generalized power transfer system 10″, 410 for supplying power from a DC source 420 to a power load 70 includes a radio frequency power amplifier 26B″ in wired electrical communication with the power source 420 and configured to convert the DC voltage from the source 420 into an AC voltage signal having an oscillating frequency; a rectifier configured to receive the transferred power from the power amplifier 26B″, and a receiver controller 42″ in communication with the rectifier 46D, the receiver controller being configured to adjust the efficiency of the power transfer from the power amplifier 26B″ to the rectifier 46D by adjusting the current-voltage phase characteristic of the rectifier 46D. The receiver controller 42″ may be configured to automatically adjust the current-voltage phase characteristic of the rectifier 46D. The rectifier may be a differential self-synchronous radio frequency rectifier.

[0403] The power transfer system 10", 410 may further include a load management system 46E" in wired communication with the load 70" and power disposed between the load 70" and the rectifier 46D, where the load management system 46E" is configured to increase the efficiency of the power transfer by adjusting the input impedance of the rectifier 46D. The load management system 46E" may be configured to automatically adjust the input impedance of the rectifier 46D.

[0404] The power transfer system 10", 410 may further include a transmitter controller 22" in communication with the amplifier 26B", the transmitter controller 22" configured to increase the efficiency of the power transfer by adjusting the current-voltage phase characteristic of the amplifier 26B. The transmitter controller 22" may be configured to automatically adjust the current-voltage phase characteristic of the amplifier 26B to increase the efficiency of the power transfer.

[0405] The power transfer system 10", 410 may further include an oscillator 26A" in communication with the amplifier 26B" and the transmitter controller 22". The transmitter controller 22" may be configured to adjust the oscillation frequency via the oscillator 26A.

[0406] The power amplifier 26B may be in direct wired radio frequency communication with the adjustable phase radio frequency rectifier 46D (via connection 60 in FIG. 19B ). The power amplifier 26B″ may be in wireless near-field radio frequency communication with the adjustable phase radio frequency rectifier 46D. The power transfer system 10″, 410 may include a transmitter resonator 30″ in wired radio frequency communication with the power amplifier 26B″ and a receiver resonator 50″ in wired radio frequency communication with the rectifier 46D. The transmitter resonator 30″ and the receiver resonator 50″ may be in wireless near-field radio frequency communication with each other. The power amplifier 26B″ may be in at least one of capacitive near-field wireless and inductive near-field wireless radio frequency communication with the rectifier 46D. The power amplifier 26B″ may be in bimodal near-field wireless radio frequency communication with the rectifier 46D.

[0407] The power transfer system may further include a power conditioning unit 430 electrically disposed between the power source 420 and the power amplifier 26B, and configured to adjust at least one of the current and voltage from the power source 420 to improve the efficiency of the power transfer.

[0408] In another embodiment described with reference to FIGS. 19A, 19B, 27A and 27B, and 28A and 28B, an electric power system comprises a mechanical load bearing structure 510, 630 having a first portion that is electrically conductive, a power load, and a power transfer system 10", 410 comprising at least one high frequency resonator 30", 50" configured for near-field wireless power transfer, the resonator comprising an at least partially electrically conductive first portion. The electric power system may further comprise a rechargeable battery 520, the power load may comprise an electric motor 530, the electric power system may be an electric vehicle 500, 500', the mechanical load bearing structure may comprise a chassis 510 of the vehicle 500, the electric power system may be a display monitor 610, and the mechanical load bearing structure may be at least one of a frame 630 and a base of the monitor 610.

[0409] The power supply system may further include a power source. The power transmission system may include a high frequency power amplifier 26B" in wired electrical communication with the power source and configured to convert a DC voltage from the power source. an adjustable phase radio frequency rectifier 46D in wired electrical contact with the power load 70 and in radio frequency communication with the power amplifier 26B; the rectifier 46D" configured to receive the transferred power from the amplifier 26B"; and a receiver controller 42" in communication with the rectifier 46D and configured to adjust the efficiency of the power transfer from the amplifier 26B" to the rectifier 46D by adjusting the current-voltage phase characteristic of the rectifier 46D.

[0410] In another embodiment, as shown in FIGS. 19A and 19B, 27A and 27B, and 28A and 28B, an apparatus includes a mechanical load-bearing structure 510, 630 having an electrically conductive first portion; a power source; a power load 70″, 530, 610; a radio frequency power amplifier 26B configured to convert a DC voltage from the power source into an AC voltage signal having an oscillation frequency; an adjustable phase radio frequency rectifier 46D in wired electrical contact with the power load 70 and in radio frequency communication with the power amplifier 26B; the rectifier 46D″ configured to receive power transferred from the amplifier 26B″; and a receiver controller 42″ configured to adjust the efficiency of power transfer from the amplifier 26B to the rectifier 46D by adjusting the current-voltage phase characteristic of the rectifier 46D, the electrically conductive first portion being positioned to carry at least one of the power from the amplifier 26B and the rectifier 46D.

[0411] The apparatus may further include a load management system 46E" in wired communication with the load 70" and a power distribution system disposed between the load 70" and the rectifier 46D and the load management system 46E" configured to increase the efficiency of power transfer by adjusting the input impedance of the rectifier 46D. The apparatus may further include a transmitter controller 22" in communication with the amplifier 26B" and a transmitter controller 22' configured to increase the efficiency of power transfer by adjusting the current-voltage phase characteristic of the amplifier 26B. The apparatus may further include an oscillator 26A" in communication with the amplifier 26B" and a transmitter controller 22' configured to adjust the oscillation frequency via the oscillator 26A.

[0412] The power amplifier 26B can be in direct wired radio frequency communication with the rectifier 46D via the conductive first portion. The power amplifier 26B can be in wireless near-field radio frequency communication with the rectifier 46D. The power transfer system 10", 410 can include a power amplifier 26B" in wired radio frequency communication with the rectifier 46D and a transmitter resonator 30" in wired radio frequency communication with a receiver resonator 50", one of the transmitter resonator 30" and the receiver resonator 50" can include a conductive first portion. The transmitter resonator 30" and the receiver resonator 50" can be in wireless near-field radio frequency communication with each other. The power amplifier 26B" can be in at least one of capacitive near-field wireless and inductive near-field wireless radio frequency communication with the rectifier 46D. The power amplifier 26B" may be in bimodal near-field wireless radio frequency communication with the rectifier 46D. The DC source may comprise a rechargeable battery 520 and the load may comprise an electric motor 530.

[0413] In a further embodiment, shown schematically in Figure 32, based on Figures 6, 7, 8 and 9, there is provided an sealed bidirectional power transfer circuit device 800 having a sealed device 800 within its sealed interior, with a plurality of terminals arranged for electrical communication with devices external to the sealed device 800: the MPS device 810 has at least one DC terminal, at least one AC terminal and at least one control terminal, the MPS device 810 is adjustable between amplification and rectification conditions and is configured to bidirectionally communicate DC voltage and DC current via the at least one DC terminal. bidirectionally communicating a radio frequency power signal having an amplitude, frequency, and phase via at least one AC terminal, and in wired data communication with a controller 880, the radio frequency power signal having an amplitude, frequency, and phase; a duty cycle adjustment (PDFCA) circuit 820 in wired electrical communication with the MPS device 810 via at least one control terminal, the PDFCA circuit 820 being arranged to establish a radio frequency oscillating signal having a frequency and phase of the radio frequency power signal at the at least one control terminal of the MPS device 810, and being configured to adjust the MPS device 810 between an amplification condition and a rectification condition by adjusting the phase of the radio frequency oscillating signal under command of the controller 880. The PDFCA circuit 820 may be further configured to establish a duty cycle of the radio frequency oscillating signal. The PDFCA circuit 820 may include a radio frequency oscillator for generating the radio frequency oscillating signal under command from the controller 880. The term "multi-terminal power switching device" is used herein to describe a device having at least three terminals and capable of switching or modulating current flowing between at least two terminals of the device based on a signal applied to at least a third terminal of the device.Suitable MPS devices 810 include, but are not limited to, mechanical relay switches, solid-state switches, electro-optical switches (also called optical switches, thyristors, or waveguide switches), transistors (including, for example, MOSFETs, MESFETs, III-V semiconductor transistor devices, and BJT devices), and power tube devices, including, for example, triodes and pentodes.

[0414] In some embodiments, the circuit is encapsulated with a polymer coating or mold to create an encapsulated device. In some embodiments, the encapsulated device protects components disposed within the device. In some embodiments, encapsulating the device provides electrical insulation to prevent electrostatic discharge, short circuits, or other harmful discharges that could damage the device components. In some embodiments, encapsulating the device protects internal components from oxidation. In some embodiments, the encapsulation may form a watertight or water vapor barrier. In some embodiments, the encapsulation facilitates electrical connections to the device by providing access to one or more terminals on the exterior of the encapsulated device.

[0415] The encapsulated power transmission circuit device 800 may further include a tuning network 830 within its encapsulated interior in wired data communication with a controller 880 that regulates the network 830 in wired electrical communication with the MPS device 810 via at least one AC terminal, the tuning network 830 being configured to tune the radio frequency power signal from the tuning network 830 to a conditioned radio frequency power signal when the MPS device 810 is in an amplification condition. The tuning network 830 may include a harmonic termination network circuit of the type shown in FIGS. 8 and 9 arranged to suppress harmonics of the radio frequency oscillation signal in the high frequency power signal. As shown in FIGS. 8 and 9, the harmonic termination network may include one or more inductors and one or more of a first harmonic termination 1271, 147G, a second harmonic termination 124H, 147F, and a third harmonic termination 127F, 147D.

[0416] The enclosed power transmission circuit device 800 may include an amplitude / frequency / phase detector (AFPD) within its sealed interior in wired data communication with the controller 880. 840 is disposed in wired electrical communication with the tuning network and is configured to determine the amplitude, frequency, and phase of any radio frequency power signal communicated between the tuning network and an AC load / source external to the sealed device. To this end, in another embodiment not shown in Figure 32, PDFCA circuit 820 measures the signal amplitude, frequency, and phase at the output of tuning network 830, not shown in Figure 32, which is configured to adjust at least one of the radio frequency oscillating signal and / or DC current and DC voltage based on a feedback signal received directly from AFPD 840.

[0417] The tuning network 830 may comprise a voltage-current tuner for adjusting the phase difference between the voltage and current of the tuned radio frequency signal based on measurement data from the AFPD 840 when the power switching device is in an amplifying condition. A suitable voltage-current tuner is described in detail with reference to Figure 32, where the voltage-current tuner of the tuning network 830 is applied to signals destined for signal connections leading out of the device 800, thereby functioning as a tuner when power is transmitted downward through the device 800 of Figure 32, and the voltage-current tuner may be transparent to power transmitted in the opposite upward direction through the device 800 of Figure 32, where the power transfer circuit device 800 is bidirectional. In some implementations, tuning network 830 may communicate a tuning radio frequency power signal with AC load / source 900, which may be transmitter resonators 30 and 30", as described with respect to FIGS. 6 and 19A, 27A, and 27B. When AC load / source 900 is such a bimodal transmit resonator, the voltage-current tuner may function to adjust the ratio of the magnetic field to the magnetic field, as described with respect to FIG. 6.

[0418] The sealed power transmission circuit device 800 may further comprise, in wired data communication with the controller 880, for adjusting the DC power communicated between the MPS 810 and the DC source / load 700 based on measurement data communicated to the controller by the AFPD 840 within the sealed interior in wired electrical communication between the MPS 810 and the DC source / load 700 external to the MPS 810 and the external DC source / load 700. In other embodiments not shown in FIG. 32 , the PM circuit 860 may be arranged to adjust the communicated DC power. between the MPS 810 and the DC source / load 700 based on feedback signals received directly from the AFPD 840 and / or VID 850.

[0419] Note that DC power can be transferred bidirectionally through the PM circuit 860 between the MPS 810 and the DC source / load 700. Note that while the DC source / load 700 is described herein as a "source / load," it is emphasized that when the DC source / load 700 is acting as a source of DC power, the AC load / source 900 is acting as a load for power converted to AC power, and vice versa. The arrows drawn adjacent to and parallel to the connectors in FIG. 32 indicate the path and direction of power flow through the device 800 when the MPS 810 is in either its amplifying or rectifying condition. When the MPS 810 is in the amplifying state, power flow is downward through FIG. 32, and when the MPS 810 is in the rectifying state, power flow is upward through FIG. 32.

[0420] The enclosed power transfer circuit device 800 may further be provided within its sealed interior in wired data communication with a voltage / current detector (VID) 850 of the controller 880 arranged to determine the DC voltage and DC current flowing between the MPS 810 and the PM circuit 860, and may be adjusted based on the measurement of the VID 850 such that when the MPS 810 is in an amplifying condition, the device 800 presents to the DC source / load 700 an equivalent DC load that allows maximum power extraction from the DC source / load 700. A DC voltage at at least one DC terminal of the MPS device 810 is regulated. When the MPS 810 is in a rectifying state, the power transfer circuit device 800 may be adjusted based on the measurement of the VID 850 such that the device 800 presents to the DC source / load 700 an equivalent DC source impedance that allows maximum power transfer from the device 800 to the DC source / load 700, thereby regulating the DC voltage at the wired connection between the device 800 and the DC source / load 700.

[0421] The sealed power transmission circuit device 800 is in wired data communication with the controller 880, the AFPD 840, and the VID 850, and is configured to receive and store signal data from the two detectors 840 and 850 in a sealed internal memory 870, and provide the signal data from the two detectors 840 and 850 to the controller 880. The memory 870 may be capable of storing the complete state of the device 800 for a series of consecutive instants in time.

[0422] The tuning network may further comprise one or more of a compensation network, a matching network, and a filter. The compensation network 26E, the matching network 26D, and the filter 26C of FIG. 6 are suitable for this purpose, and the options are not limited to the devices of FIG.

[0423] The encapsulated power transmission circuit device 800 may be provided with an encapsulated internal controller 880, or in other embodiments, the encapsulated power transmission circuit device 800 may use an external controller having appropriate input / output facilities for communicating data with the various circuits incorporated within the encapsulated interior of the device 800, and appropriate software or firmware may be programmed into the controller to carry out all of the control procedures described above.

[0424] The sealed power transfer circuit device 800 may further include at least one communication circuit 890 operating over one or more of Bluetooth®, WiFi, ZigBee®, and cellular technologies for communicating information bidirectionally between the controller 880 and devices external to the sealed power transfer circuit device 800, and one or more antennas 894 may be disposed within the sealed interior of the device 800, although one or more of the external devices may be other power transfer circuit devices, including, for example, other devices 800, and the one or more other devices may form part of an aggregate power transfer system, for example, as described above in other embodiments of FIG.

[0425] The PDFCA circuitry may be configured to adjust the duty cycle of the radio frequency oscillating signal based on measurements by the AFPD 840 and the VID 850. In some embodiments, information about the measurements may be forwarded to the controller 880 and from there to the PDFCA circuitry 820, which then adjusts the duty cycle of the radio frequency oscillating signal based on the received information. In other embodiments not shown in FIG. 32, a feedback signal may be passed directly from the AFPD 840 and the VID 850 to the PDFCA circuitry 820, which adjusts the duty cycle of the radio frequency oscillating signal based on the received feedback signal. By changing the duty cycle of the radio frequency oscillating signal, the PDFCA circuit 820 can adjust the direction of power flow through the device 800, such that when power flows from the DC source / load 700 through the device 800 to the AC load / source 900, the PDFCA circuit 820 can adjust the DC power delivered to the device 800 by the power source / load 700, and when power flows from the device 800 to the DC source / load 700, the PDFCA circuit 820 can adjust the AC power delivered to the device 800 by the AC load / source 900 and the power delivered to the DC source / load 700 by the device 800.

[0426] Controller 880 may be in bidirectional wired communication with external devices and circuits 898 (labeled Ext.) In FIG. 32 , located external to the enclosed interior of device 800, this wired communication may be employed, for example, but not limited to, to exchange data or to provide system clock synchronization signals to controller 880 for a system in which device 800 may be incorporated.

[0427] 6 and 7, sensors and detectors 24A, 24B, 24C and 24D may be usefully positioned outside the sealed interior of device 800.

[0428] 6 and 7 , the power channel physically extends from the wired connection between the DC source / load 700 and the PM circuit 860, through the PM circuit 860, the VID 850, the MPS device 810, and the tuning network 830, to the AC load / source 900. Along the physical power channel, the PM circuit 860, the MPS device 810, and the tuning network 830 are all under the control of the controller 880, which controls the MPS device 810 via the PDFCA circuit 820, and the controller may modulate radio frequency power signals in the tuning network 830 and / or the MPS device 810 itself. The controller may also be configured to induce modulation of the DC voltage between the PM circuit 860 and the DC source / load 7000, thereby allowing information to be modulated onto the radio frequency power signal, the tuned radio frequency power signal, and / or said DC voltage, whereby other devices may include additional bidirectional power transfer circuit device 800 and information, in digital or analog form, may be modulated onto the radio frequency power signal, the tuned radio frequency power signal, and / or said DC voltage. In other embodiments, information may be modulated onto the frequency. This is different from the case of power transmission. In other embodiments, information may be modulated onto a harmonic of the frequency of the power signal. In yet another embodiment, the frequency of the high frequency power signal may be a harmonic of the frequency of the signal onto which the information is modulated. The above description already illustrates how the tuning network 830 subsystem may be employed as a suitable modulator.

[0429] Having described above how device 800 can be reconfigured between transmitter mode and rectification mode, and how power channels can be modulated, it should be apparent that device 800 can function as a full-duplex transmit-receive system for transmitting information in both directions. When two devices 800 are used in modules 20 and 40 of FIG. 1, system 10 of FIG. 1 can include an additional secondary similar to secondary 14 of FIG. 1, and when an additional secondary 14 is present, the above configuration is similar for the systems shown in FIGS. 20A-22B and 27A-28B between transmitter module 20" and receiver module 40" used in the systems of FIGS. 19A and 19B.

[0430] Information transmitted in the manner described herein may include, but is not limited to, the operating mode of the MPS device 810, the number and type of additional devices 810, ambient object sensor information, and load status monitoring information including, for example, battery charge state, load voltage, and load current.

[0431] The electronic circuitry of the encapsulated bidirectional power transmission circuit device 800 may be implemented in a variety of device fabrication techniques, including, but not limited to, as several separate devices on a suitable circuit board, as a flip-chip arrangement of one or more separate devices bonded active face-down onto a silicon-based circuit, or as a single monolithic integrated circuit device, as a hybrid circuit bonded or mounted on a suitable substrate material. Figure 33 shows a flip-chip configuration in which the bidirectional power transmission circuit device 800 of Figure 32 is mounted in a separate semiconductor crystal and then flip-chip mounted via solder bumps on pads 808. The MPS device 810 may be fabricated, for example, but not limited to, as a separate higher power device in a wide bandgap semiconductor crystal. Pads 808 are formed on a silicon wafer 801 that also contains the balance of the subsystems of device 800 of FIG. 32, and two pads 806 for connection to devices 700 and 900 shown in FIG. 32 are for connecting controller 880 and communication circuitry 890 to devices and antennas external to device 800.

[0432] In one particular embodiment shown in FIG. 34A, the electronics of the encapsulated bidirectional power transfer circuit device 800 may be implemented within a single silicon monocrystalline wafer 812 in conjunction with at least one photovoltaic cell 814 that functions as the DC source / load 700 of FIG. 32.

[0433] In a further embodiment, further described with reference to FIG. 34B, the electronics of the encapsulated bidirectional power transmission circuit device 800 may be implemented within a single silicon single crystal wafer 812, as described above with reference to FIG. 2B and with a resonator structure 180′ of the type described in more detail with respect to FIGS. 2A-5 acting as an AC load / source 900 on the surface of the silicon single crystal wafer 812, together with at least one photovoltaic cell 814 acting as the DC source / load 700 of FIG. An antenna 894 for use with Bluetooth®, WiFi, ZigBee®, and cellular technologies may also be integrated on the same single silicon monocrystalline wafer. The antenna 894 is not shown in FIG. 34B. In FIGS. 34A and 34B, a connection 818 connects the resonator 180′ to the tuning network 830 of the device 8000, and the resonator 180′ can act as a heat sink or heat dissipator for heat generated within the device 800 or absorbed by the solar cell 814; for this purpose, the resonator 180′ can use air as a dielectric and simultaneously as a coolant fluid.

[0434] In other embodiments, the DC load 70" of Figures 19A and 19B may be replaced by an AC load 70" in both cases, as shown in Figures 35A and 35B, respectively. The remaining systems 10" and 410 of Figures 35A and 35B may be the same as systems 10" and 410 of Figures 19A and 19B. The oscillator 26A" of Figures 19A and 19B may, in other embodiments, be set to the frequency and phase required by the AC load 70" of Figures 19A and 19B, and the transmitter controller 22" may be programmed to set the oscillator 26A" to the frequency and phase required by the AC load 70".

[0435] In yet other embodiments of the system of FIGS. 35A and 35B, the AC load 70′ may be a power grid to which the system of FIGS. 35A and 35B is configured to deliver power. In such a grid-supplied configuration, it is important to control the frequency, phase, and voltage level of the signal supplied by the system of FIGS. 35A and 35B to the power grid 70′. To this end, the information feedback mechanism already described above may be used to send information to the power transmitter controller 22 regarding the required frequency, phase, and voltage level of the power grid. This information may be in digital or analog format. In some embodiments of the wired system of FIG. 35B, additional signal lines (not shown to avoid clutter) may be taken from the AC power grid 70′ to the transmitter controller 22 or directly to the oscillator 26A′ to enable the transmitter module 20 to directly track the AC load 70′ in terms of frequency and phase, thereby imposing constraints required by the power grid 70′ on the output signal of the system of FIG. 35B. These constraints may include modulation of the output signal of the load management system 46E to meet the requirements of the power grid 70′. The modulation may be at a frequency equal to the frequency of the power grid and at a phase and voltage level that transfers power to the power grid 70'.

[0436] FIG. 36 illustrates an embodiment of the system of FIG. 32 in which the AC load / source 900 of FIG. 32 is an AC power grid 900′. In this embodiment, similar to the systems of FIGS. 35A and 35B, information regarding the required frequency, phase, and voltage levels of the power grid can be sent back to the controller 880, which can then adjust the signal at the control terminal of the MPS device 810, via the phase, frequency, and duty cycle adjustment (PDFCA) circuit 820, to meet the power transfer requirements imposed by the power grid 900′. These requirements can include modulation of the output signal of the tuning network 830 to meet the requirements of the power grid 70″. The modulation can be at a frequency equal to the frequency of the power grid and at a phase and voltage level that transfers power to the power grid 70′. Although the system of FIG. 36 is bidirectional in nature, this configuration allows it to act as a mechanism for transferring power to an AC power network.

[0437] 20A and 20B, 21A and 21B, and 22A and 22B, each solar cell 420 may be equipped with a sensor to determine the operating state of the solar cell 420, which may include, but is not limited to, power level, voltage level, current level, temperature, and other performance parameters. The operating status may be transmitted to the receiver module 40 via the transmitter module 20 associated with the solar cell 420, and the operating status of the transmitter module 20 may similarly be sensed and transmitted to the receiver module 40 via the transmitter module 20. Referring to FIG. 33 and FIGS. 34A and 34B, appropriate sensors may also sense performance parameters of the encapsulated bidirectional power transfer circuit device 800 and the multi-terminal power switching (MPS) device 810, and transmission of load information via the MPS device 810 has already been described. Information regarding the performance parameters of the devices 800 and 810 may similarly be transmitted throughout the system.

[0438] Figures 37A and 37B show two configurable bidirectional power transfer systems for transferring power from a DC source, according to some embodiments. Figures 37C and 37D show several different embodiments of configurable bidirectional power transfer systems for transferring power between a DC source and a variable load. The variable load can be an AC load (in both Figures 37A and 37B), a DC load (Figure 37B), or a load carrying a mixture of AC and DC power (Figure 37B).

[0439] FIG. 37A illustrates a system 950 for transferring power between a DC source 1028 and an AC load 1070. The system is useful for transferring power from a DC source to an AC power grid operating at a typical line frequency of about 50 or about 60 Hz. The system 950 can also be configured to transfer power in the opposite direction. Similar to FIGS. 19A, 19B, 35A, and 35B, the system 950 of FIG. 37A is based on the controlled function of self-synchronous radio frequency rectifier / amplifiers 1025A and 105B, where the devices 1025A and 105B are reconfigurable between amplifier and rectifier modes. The devices 1025A and 105B may be the same as or similar to the self-synchronous radio frequency rectifier / amplifier 26B of FIGS. 6 and 8, and the rectifier 46D of FIGS. 7 and 9 may comprise a switch-mode self-synchronous radio frequency rectifier / amplifier.

[0440] In the first embodiment, a central controller 1080 is used. The controller 1080 may include protection circuitry for the system. In other embodiments, distributed controllers may be employed for the same purpose. When power is being transferred from the DC source / load 1028, the devices 1025A and 1025B are placed in amplification mode, and their switching operation is driven by a switching signal provided by the HF switching signal generator 1024. Signal generator 1024 provides the frequency for the switching signal driving devices 1025A and 1025B, controls the switching duty cycle of devices 1025A and 105B, and ensures that the switching patterns of devices 1025A and 105B have a controlled mutual phase and pulse width relationship.

[0441] In the systems of Figures 37A and 37B, HF switching signal generator 1024 provides one switching signal to each of devices 1025A and 108B. In more general systems, such as those described below with respect to Figures 37C and 37D, there may be multiple pairs of self-synchronizing radio frequency rectifier / amplifiers that are provided with switching signals by an HF switching signal generator similar to HF switching signal generator 1024, and the number of HF switching signal generators used in any given embodiment may vary. For example, one HF switching signal generator may provide switching signals to a pair of self-synchronizing radio frequency rectifier / amplifiers. One HF switching signal generator may provide switching signals to multiple pairs of self-synchronizing radio frequency rectifier / amplifiers.

[0442] The HF switching signal generator 1024 can be controlled by the controller 1080 to drive the differential self-synchronous radio frequency rectifier / amplifier 1025A (in amplifier mode) with a first switching signal at a first frequency f A. Simultaneously, the HF switching signal generator 1024 can be controlled by the controller 1080 to drive the differential self-synchronous radio frequency rectifier / amplifier 105B (in amplifier mode) with a second switching signal at a second frequency of a second f e. fn=fA+Af (Equation 1) In Equation 1, the difference frequency Af between the frequency of the second switching signal and the frequency of the first switching signal is twice the frequency at which the transmitted power is intended to be supplied to the AC load / source 1070.

[0443] In embodiments where the AC load 1070 is not carrying a power signal in the absence of the system 950, the frequencies f and f, and thereby the difference frequency A, may simply be set in or by the HF switching signal generator 1024, and the frequencies f and f may differ from each other by a difference frequency A that is twice the frequency of the power signal intended for injection into the AC load 1070, and in some embodiments, the frequencies f and f may be set in the HF switching signal generator 1024 by the controller 1080 based on design choice.

[0444] In other embodiments where an existing AC power signal is present at the AC load 1070, such as a residential power grid, the switching signal frequencies ε and ε can be set in the HF switching signal generator 1024 by sensing the operating frequency fc of the AC load / source 1070 and forwarding a reference signal at frequency fc to the HF switching signal generator 1024 via an optional isolator system 1090 and a phase-locked loop 1095. The term “load information circuit” is used herein to describe this segment of the circuit. To distinguish this additional section of the circuit from the circuit used when there is no existing power signal at the AC load / source 1070, this load information circuit and its components are shown with dashed lines in FIG. 37A . The direction of reference signal flow within that circuit is given by the arrows in FIG. 37A . The optional isolator system 1090 may be included for some regions under some circumstances. When the load is not carrying a power signal, some regions may require adjusted isolation from the AC load / source 1070. The optional isolator system 1090 may comprise an air gap. Those skilled in the art will recognize how to use isolators to provide data and timing signals, and the details will not be described herein. In other embodiments, instead of using a reference signal, information may be communicated to the HF switching signal generator 1024 about at least one of the DC level, frequency, and phase of the power signal at the load.

[0445] HF switching signal generator 1024 can double the sensed frequency f to determine the required difference frequency F between frequencies F and F, and can apply switching signals to devices 104A and 105B at the resulting frequencies F and A. In such an embodiment, the process of sensing the operating frequency f of AC load / source 1070, transferring the signal to HF switching signal generator 1024, and doubling its operating frequency f may all occur under the control of controller 1080; to avoid cluttering FIG. 37A, control lines running from controller 1080 to the devices it senses or controls, including devices 1025A and 109B, are not shown. Note that the switching signal frequencies ΔB and ΔA only need to differ by A=2f, and the difference frequency A can be determined according to equation (1) above. Two suitable frequencies FB and AA, which differ from each other by F f=2f t, can be determined in the HF switching signal generator 1024, and the arrangement described here helps the power supplied from the DC source 1028 to be in phase with the grid load, thereby enabling efficient power transfer.

[0446] In some embodiments, the switching signals of the driving devices 1025A and 105B may be selected to be in the range of 1 MHz-1 GHz. In some embodiments, the first and second switching signals of 950 may be selected to be in the range between 100 kHz and 1 GHz. In some embodiments, they may be selected to be in the ISM band previously described in this disclosure. The term high frequency (HF) is used herein to describe frequencies between approximately 100 kHz and 1 GHz. The devices 105B and 1025A may transmit any power drawn from the DC source / load 1028 at frequencies f and f, respectively, via the HF power link system 1065 to the switch mode rectifier 1067, whose opera...

Claims

1. 1. A system for transferring power from at least one DC power source to a variable load, comprising: a corresponding radio frequency power module in electrical communication with and positioned proximate to each of the at least one DC power source; a single aggregator configured to receive through all of the at least one RF power module power from a corresponding at least one DC power source; each of the at least one high frequency power module comprises a high frequency (HF) switching signal generator and a pair of differential self-synchronous radio frequency rectifier / amplifiers; both of the rectifier / amplifiers in the pair are in wired electrical communication with a DC power source corresponding to at least one of the radio frequency power modules and are configured to extract power from the corresponding DC power source; The system, wherein the HF switching signal generator is configured to provide switching signals to corresponding pairs of the differential self-synchronous radio frequency rectifier / amplifiers.

2. 1. A circuit for transferring power from at least one DC power source to a variable load, comprising: a single aggregator configured to receive power output from at least one corresponding DC power source via all of the at least one RF power module; each said high frequency power module has a power output and includes a high frequency switching signal generator and a pair of differential self-synchronous radio frequency rectifier / amplifiers, said high frequency switching signal generator configured to send a switching signal to a corresponding pair of said differential self-synchronous radio frequency rectifier / amplifiers, each said differential self-synchronous radio frequency rectifier / amplifier having a wired connection to a corresponding one of at least one DC power source.

3. 3. The system or circuit of claim 1 or claim 2, wherein all of the high frequency power modules are phase locked to one another.

4. 4. A system or circuit as claimed in any one of claims 1 to 3, wherein all of the at least one high frequency power modules are phase locked to one another via a phase locked loop to an AC power signal at a variable load.

5. 5. The system or circuit of claim 1, wherein the phase-locked loop is incorporated into the corresponding high frequency power module.

6. 6. The system or circuit of claim 1, wherein each of the at least one high frequency power modules comprises an HF link in wired electrical communication with both of the differential self-synchronous radio frequency rectifier / amplifiers for receiving and mixing power signals from the two differential self-synchronous radio frequency rectifier / amplifiers and transmitting based on the mixed power signal.

7. 7. The system or circuit of claim 1, wherein each of the at least one high frequency power modules comprises a switch mode rectifier in wired electrical communication with the HF link, the switch mode rectifier arranged and configured to receive and rectify the mixed power signal and transmit the rectified power signal via wire.

8. 8. The system or circuit of claim 1 , wherein each of the at least one radio frequency power module comprises a deployment circuit positioned and configured to receive a rectified power signal from the switch mode rectifier, deploy the rectified signal, and transmit over a wire based on the deployed power signal.

9. 1. A system or circuit including a bimodal wireless near-field HF link system, comprising: each of the at least one high frequency power module includes a primary side of one HF link in wired electrical communication with both of the differential self-synchronous radio frequency rectifier / amplifiers in the at least one high frequency power module; the system comprises a single collective secondary of an HF link system configured to receive power from all of the at least one HF link primaries; 9. A system or circuit according to claim 1, wherein the secondary side comprises a single receiver resonator and a single receiver module.

10. the receiver module is contained within the aggregator along with a switch-mode rectifier and unfolding circuitry; the switch-mode rectifier is in wired electrical communication with the receiver module and the unfolding circuitry and receives and rectifies the mixed power signal from the receiver resonator; 10. The system or circuit of claim 1, wherein the deployment circuit is in wired electrical communication with a junction unit and is configured to receive and deploy a rectified power signal from the rectifier and provide it to a variable load.

11. 11. A system or circuit as claimed in any one of claims 1 to 10, characterized in that the switching signals supplied by the HF switching signal generator to the two differential self-synchronous radio frequency rectifier / amplifiers differ by one of a predetermined frequency difference and a predetermined phase difference.

12. 1. A system or circuit including a controller, 12. The system or circuit of claim 1, further comprising: a controller configured to communicate to the HF switching signal generator at least one of a frequency and a phase determined by the controller based on information about the load and information about the DC source.

13. 13. The system or circuit of claim 1, wherein the high frequency power module comprises the controller.

14. the at least one DC source is a photovoltaic cell; The system includes a planar transparent solar cover having planar first and second solar cover surfaces, and a frame to mount the transparent solar cover; 14. The system or circuit of claim 1, wherein the at least one photovoltaic cell is disposed on the first solar cover surface, with a flat light-sensitive surface of the at least one solar cell facing the first solar cover surface.

15. 15. A system or circuit according to any one of claims 1 to 14, characterized in that each high frequency power module comprises a high frequency power circuit on a printed circuit board in wired electrical communication with a corresponding at least one photovoltaic cell.

16. 16. The system or circuit of claim 1, wherein the high frequency power circuit is disposed on a plane of the printed circuit board facing away from the first solar cover surface.

17. 17. The system or circuit of claim 1, further comprising a conformal encapsulation layer coupled to the first solar cover surface and covering the at least one photovoltaic cell and the corresponding radio frequency power module.

18. 18. The system or circuit of claim 1, further comprising a dielectric protective cap over the high frequency power circuit.

19. 19. A system or circuit according to any one of claims 1 to 18, characterized in that the protective cap is disposed on a conformal encapsulation layer.

20. 20. The system or circuit of claim 1, wherein the protective cap is disposed below a conformal encapsulation layer.

21. 21. The system or circuit of claim 1, wherein the periphery of the protective cap is sealed to the conformal encapsulation layer with the protective cap positioned below and protruding through the conformal encapsulation layer.

22. 22. The system or circuit of claim 1, wherein the printed circuit board is positioned in close proximity to the corresponding at least one photovoltaic cell.

23. 23. A system or circuit according to any one of claims 1 to 22, characterized in that the printed circuit board is arranged on an insulating layer arranged on the back surface of the photovoltaic cell.

24. 24. A system or circuit according to any one of claims 1 to 23, characterized in that the at least one photovoltaic cell is arranged in an array.

25. 25. The system or circuit of claim 11, wherein the planar first solar cover surface comprises an optically transparent polymer layer.

26. disposing, on the first planar surface of the transparent solar cover, at least one photovoltaic cell having a photosensitive surface facing the first planar surface of the transparent solar cover, and a radio frequency power module comprising a PC board and a radio frequency power circuit in communication with the at least one photovoltaic cell for collecting power from the at least one photovoltaic cell, the radio frequency power circuit being disposed on the PC board on the planar surface facing away from the transparent solar cover; disposing a heat-deformable polymer sheet extending across a surface area of ​​the transparent solar cover from a first surface of the transparent solar cover opposite the at least one photovoltaic cell to form a laminate stack in a plane; transferring the lamination stack to a vacuum oven; establishing a vacuum in a vacuum oven to remove air between layers of the laminate stack; heating the laminate stack to a deformation temperature of the heat-deformable polymer sheet; applying pressure to the stack perpendicular to said plane; restoring ambient air pressure in the vacuum oven to adhere the heat deformable polymer sheet to the transparent solar cover and conformally force the heat deformable polymer sheet onto the at least one photovoltaic cell and the radio frequency power module to form a packaged array of photovoltaic modules; mounting the packaged array of photovoltaic modules within a frame; A method for manufacturing a solar panel comprising:

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