Control circuit for converter and electronic device

Abstract

This control circuit for a direct current (DC) to DC converter may include a pulse width modulation (PWM) controller for generating a PWM signal applied to a gate of a transistor in the DC to DC converter. The control circuit may include a lumped element connected to an adjustment pin of the PWM controller for adjusting a switching frequency of the PWM signal which controls a time when the gate is driven. The control circuit may include a first resistor to which a driving voltage of the PWM controller is applied. The control circuit may include a diode connected to the first resistor. The control circuit may comprise: a capacitor arranged in parallel between the diode and the adjustment pin; and a second resistor for discharging the capacitor.

Description

Control circuits and electronics for converters

[0001] The descriptions below relate to the control circuit and electronics for the converter.

[0002] An electronic device can obtain power from an external source. For example, the power may include voltage. For example, the electronic device can perform conversion of the power obtained from the external source. For example, the electronic device can include a converter for converting the power. For example, the electronic device can utilize power converted within the electronic device.

[0003] A control circuit for a DC (direct current)-DC converter may include a PWM controller for generating a PWM signal applied to a gate of a transistor in the DC-DC converter. The control circuit may include a lumped element connected to a control pin of the PWM controller for adjusting an operating frequency (switching frequency) of the PWM signal that controls a time for which the gate is driven. The control circuit may include a first resistor to which a driving voltage of the PWM controller is applied. The control circuit may include a diode connected to the first resistor. The control circuit may include a capacitor arranged in parallel between the diode and the control pin, and a second resistor for discharging the capacitor.

[0004] An electronic device may include a direct current (DC)-DC converter. The electronic device may include an electronic component to which a voltage converted by the DC-DC converter is applied. The electronic device may include a PWM controller for generating a pulse width modulation (PWM) signal to be applied to a gate of a transistor in the DC-DC converter. The electronic device may include a lumped element connected to a control pin of the PWM controller for adjusting an operating frequency (switching frequency) of the PWM signal that controls a time for which the gate is driven. The electronic device may include a first resistor to which a driving voltage of the PWM controller is applied. The electronic device may include a diode connected to the first resistor. The electronic device may include a capacitor arranged in parallel between the diode and the control pin, and a second resistor for discharging the capacitor.

[0005] Figure 1 illustrates an example of a wireless communication system.

[0006] Figure 2 illustrates an example of network entities according to distributed deployment.

[0007] Figure 3 illustrates an example of an electronic device that converts power supplied from an external source.

[0008] Figures 4a and 4b illustrate examples of DC (direct current)-DC converters in electronic devices.

[0009] Figure 5a shows an example of a PWM (pulse width modulation) controller for controlling a DC-DC converter and an output signal of the PWM controller.

[0010] Figure 5b shows an example of a pulse frequency modulation (PFM) controller for controlling a DC-DC converter and an output signal of the PFM controller.

[0011] Fig. 6 illustrates an example of a control circuit including a switching circuit for adjusting the operating frequency (switching frequency) of an output signal of a PWM controller.

[0012] Fig. 7 illustrates an example of a control circuit including a voltage dividing circuit for adjusting the over current protection (OCP) level of a PWM controller.

[0013] Figure 8 illustrates an example of a control circuit including a discharging circuit of a capacitor for adjusting the operating frequency.

[0014] Figures 9a and 9b illustrate examples of control circuits including a protection circuit.

[0015] Figure 10 shows an example of a control circuit connected to a DC-DC converter.

[0016] Figures 11a and 11b illustrate examples of DC-DC converters including a damping circuit.

[0017] The terms used in this disclosure are used only to describe specific embodiments and may not be intended to limit the scope of other embodiments. The singular expression may include plural expressions unless the context clearly indicates otherwise. Terms used herein, including technical or scientific terms, may have the same meaning as commonly understood by those of ordinary skill in the art described in this disclosure. Terms defined in general dictionaries among the terms used in this disclosure may be interpreted as having the same or similar meaning in the context of the relevant technology, and shall not be interpreted in an idealized or overly formal sense unless explicitly defined in this disclosure. In some cases, even if a term is defined in this disclosure, it cannot be interpreted to exclude embodiments of the present disclosure.

[0018] The various embodiments of the present disclosure described below illustrate a hardware-based approach as an example. However, since the various embodiments of the present disclosure include techniques utilizing both hardware and software, the various embodiments of the present disclosure do not exclude a software-based approach.

[0019] In the following description, terms referring to components of electronic devices (e.g., circuit, element, module, assembly, component), terms referring to signals (e.g., signal, output signal, input signal), terms referring to connections (e.g., pin, end, port, node), etc. are examples for convenience of explanation. Therefore, the present disclosure is not limited to the terms described below, and other terms having equivalent technical meanings may be used. In addition, terms such as '... part', '... device', '... thing', '... body', etc. used below may mean at least one shape structure or a unit that processes a function.

[0020] In addition, in the present disclosure, expressions such as "more than" or "less than" may be used to determine whether a specific condition is satisfied or fulfilled, but this is merely a description for expressing an example and does not exclude descriptions such as "more than" or "less than." A condition described as "more than" may be replaced with "more than," a condition described as "less than" may be replaced with "less than," and a condition described as "more than and less than" may be replaced with "more than and less than." In addition, hereinafter, "A" to "B" mean at least one of elements from A (including A) to B (including B). hereinafter, "C" and / or "D" mean at least one of "C" or "D," that is, including {"C", "D", "C" and "D"}.

[0021] Although this disclosure describes embodiments using terminology used in certain communication standards (e.g., 3rd Generation Partnership Project (3GPP)), this is merely an example for illustrative purposes. Embodiments of this disclosure can also be applied to other communication and broadcasting systems.

[0022] Figure 1 illustrates an example of a wireless communication system.

[0023] Referring to FIG. 1, FIG. 1 illustrates a base station (110) and a terminal (120) as some of the nodes utilizing a wireless channel in a wireless communication system. Although FIG. 1 illustrates only one base station, the wireless communication system may further include other base stations identical or similar to the base station (110).

[0024] The base station (110) is a network infrastructure that provides wireless access to the terminal (120). The base station (110) has coverage defined based on the distance at which a signal can be transmitted. In addition to the base station, the base station (110) may be referred to as an 'access point (AP)', 'eNodeB (eNB)', '5th generation node', 'next generation nodeB (gNB)', 'wireless point', 'transmission / reception point (TRP)', or other terms having equivalent technical meanings.

[0025] The terminal (120) is a device used by a user and communicates with the base station (110) via a wireless channel. The link from the base station (110) to the terminal (120) is referred to as a downlink (DL), and the link from the terminal (120) to the base station (110) is referred to as an uplink (UL). In addition, although not shown in FIG. 1, the terminal (120) and another terminal may communicate with each other via a wireless channel. In this case, the link between the terminal (120) and another terminal (device-to-device link, D2D) is referred to as a sidelink, and the sidelink may be used interchangeably with the PC5 interface. In some other embodiments, the terminal (120) may be operated without the involvement of a user. In one embodiment, the terminal (120) is a device that performs machine type communication (MTC) and may not be carried by the user. Additionally, according to one embodiment, the terminal (120) may be an NB (narrowband)-IoT (internet of things) device.

[0026] The terminal (120) may be referred to as a terminal, or other terms such as 'user equipment (UE),' 'customer premises equipment (CPE),' 'mobile station,' 'subscriber station,' 'remote terminal,' 'wireless terminal,' 'electronic device,' or 'user device,' or other terms having equivalent technical meanings.

[0027] The base station (110) and the terminal (120) can perform beamforming. The base station (110) and the terminal (120) can transmit and receive wireless signals in a relatively low frequency band (e.g., FR 1 (frequency range 1) of NR). In addition, the base station (110) and the terminal (120) can transmit and receive wireless signals in a relatively high frequency band (e.g., FR 2 (or, FR 2-1, FR 2-2, FR 2-3), FR 3 of NR), millimeter wave (mmWave) band (e.g., 28 GHz, 30 GHz, 38 GHz, 60 GHz)). To improve channel gain, the base station (110) and the terminal (120) can perform beamforming. Here, the beamforming can include transmission beamforming and reception beamforming. The base station (110) and the terminal (120) can impart directionality to the transmitted or received signal. To this end, the base station (110) and the terminal (120) can select serving beams through a beam search or beam management procedure. After the serving beams are selected, subsequent communication can be performed through resources that have a QCL relationship with the resource that transmitted the serving beams.

[0028] If large-scale characteristics of a channel carrying a symbol on a first antenna port can be inferred from a channel carrying a symbol on a second antenna port, the first antenna port and the second antenna port can be evaluated to have a QCL relationship. For example, the large-scale characteristics may include at least one of delay spread, Doppler spread, Doppler shift, average gain, average delay, and a spatial receiver parameter.

[0029] Although both the base station (110) and the terminal (120) are described as performing beamforming in FIG. 1, the embodiments of the present disclosure are not necessarily limited thereto. In some embodiments, the terminal may or may not perform beamforming. Furthermore, the base station may or may not perform beamforming. That is, either only one of the base station and the terminal may perform beamforming, or neither the base station nor the terminal may perform beamforming.

[0030] In the present disclosure, a beam refers to a spatial flow of a signal in a wireless channel, and is formed by one or more antennas (or antenna elements), and this forming process may be referred to as beamforming. Beamforming may include at least one of analog beamforming and digital beamforming (e.g., precoding). Reference signals transmitted based on beamforming may include, for example, a demodulation-reference signal (DM-RS), a channel state information-reference signal (CSI-RS), a synchronization signal / physical broadcast channel (SS / PBCH), and a sounding reference signal (SRS). In addition, as a configuration for each reference signal, an IE such as a CSI-RS resource or an SRS-resource may be used, and this configuration may include information associated with the beam. Information associated with a beam may mean whether the configuration (e.g., a CSI-RS resource) uses the same spatial domain filter as another configuration (e.g., another CSI-RS resource within the same CSI-RS resource set) or a different spatial domain filter, or whether it is quasi-co-located (QCL) with a reference signal, and if so, what type it is (e.g., QCL type A, B, C, D).

[0031] In the past, in communication systems with relatively large cell radius of base stations, each base station was installed to include the functions of a digital processing unit (or distributed unit (DU)) and a radio frequency (RF) processing unit (or radio unit (RU)). However, as higher frequency bands are used in 4G (4th generation) and / or subsequent communication systems (e.g., 5G) and the cell coverage of base stations becomes smaller, the number of base stations to cover a specific area has increased. The installation costs for operators to install base stations have also increased. In order to minimize the installation costs of base stations, a structure has been proposed in which the DU and RU of a base station are separated, one or more RUs are connected to one DU via a wired network, and one or more RUs are geographically distributed to cover a specific area. Hereinafter, the deployment structure and expansion examples of base stations according to various embodiments of the present disclosure are described through FIG. 2.

[0032] Figure 2 illustrates an example of network entities according to distributed deployment.

[0033] For example, the network entities may include a digital unit (DU) (210) and a radio unit (RU) (220) (or a massive multiple input multiple output (MMU) unit). For example, the network entities may be connected via a fronthaul. Unlike the backhaul between a base station and a core network, the fronthaul refers to entities (e.g., DU (210), RU (220)) between a wireless LAN and a base station. Although FIG. 2 illustrates an example of a fronthaul structure between a DU (210) and one RU (220), this is merely for convenience of explanation and the present disclosure is not limited thereto. In other words, embodiments of the present disclosure may also be applied to a fronthaul structure between one DU and multiple RUs. For example, embodiments of the present disclosure may be applied to a fronthaul structure between one DU and two RUs. Additionally, the embodiments of the present disclosure can also be applied to a fronthaul structure between one DU and three RUs.

[0034] Referring to FIG. 2, the base station (110) may include a DU (210) and a RU (220). A fronthaul (215) between the DU (210) and the RU (220) may be operated via an Fx interface. For the operation of the fronthaul (215), an interface such as an enhanced common public radio interface (eCPRI) or radio over ethernet (ROE) may be used, for example. Depending on the implementation example, the DU (210) may be referred to as a baseband unit (BBU), a digital BBU, a baseband digital unit, a digital processing unit, a digital processing circuit, a baseband processing circuit, a baseband processing unit, and / or equivalent technical terms in addition to a DU (digital unit). According to an implementation example, the RU (220) may be referred to as a remote unit, a radio demote head (RRH), a radio processing circuit, a radio processing unit, an antenna-integrated radio, an air radio device, an air scale communication device, a radio device, a radio communication device, and / or equivalent technical terms in addition to the RU (radio unit). In addition, according to an implementation example, although a network entity connected to the DU (210) in the present disclosure is described as the RU (220), it is of course possible for an MMU (massive multiple input multiple output) unit) to be connected to and used with the DU (210) instead of the RU (220).

[0035] As communication technology advances, mobile data traffic increases, significantly increasing the bandwidth requirements for the fronthaul between the digital unit and the wireless unit. In a deployment such as a centralized / cloud radio access network (C-RAN), the DU (210) performs functions for the packet data convergence protocol (PDCP), radio link control (RLC), media access control (MAC), and physical (PHY) layer, and the RU (220) can be implemented to perform functions for the PHY layer in addition to the RF (radio frequency) function.

[0036] The DU (210) may be responsible for upper layer functions of a wireless network. For example, the DU (210) may perform functions of the MAC layer and a part of the PHY layer. Here, a part of the PHY layer refers to functions performed at a higher level among the functions of the PHY layer, and may include, for example, channel encoding (or channel decoding), scrambling (or descrambling), modulation (or demodulation), and layer mapping (or layer demapping). According to an embodiment, if the DU (210) complies with the O-RAN standard, it may be referred to as an O-DU (O-RAN DU). The DU (210) may be replaced with a first network entity for a base station (e.g., gNB) in embodiments of the present disclosure, if necessary.

[0037] The RU (220) may be responsible for lower layer functions of a wireless network. For example, the RU (220) may perform a part of the PHY layer, an RF function. Here, a part of the PHY layer refers to functions of the PHY layer that are performed at a relatively lower level than the DU (210), and may include, for example, iFFT transformation (or FFT transformation), CP insertion (CP removal), and digital beamforming. The RU (220) may be referred to as an 'access unit (AU)', an 'access point (AP)', a 'transmission / reception point (TRP)', a 'remote radio head (RRH)', a 'radio unit (RU)', or other terms having an equivalent technical meaning thereto. According to an embodiment, when the RU (220) complies with the O-RAN standard, it may be referred to as an O-RU (O-RAN RU). RU (220) may be replaced with a second network entity for a base station (e.g., gNB) in embodiments of the present disclosure as needed.

[0038] In FIG. 2, the base station (110) is described as including a DU (210) and a RU (220), but the embodiments of the present disclosure are not limited thereto. The base station according to the embodiments may be implemented in a distributed deployment according to a centralized unit (CU) configured to perform functions of upper layers of an access network (e.g., packet data convergence protocol (PDCP), radio resource control (RRC)) and a distributed unit (DU) configured to perform functions of lower layers. For example, the digital unit (DU) (210) may be implemented by separating into a centralized unit (CU) and a distributed unit (DU). Between a core (e.g., 5G core (5GC) or next generation core (NGC)) network and a radio network (RAN), the base station may be implemented in a structure in which a centralized unit (CU), a distributed unit (DU), and a radio unit (RU) are arranged in that order. The interface between the CU (centralized unit) and the DU (distributed unit) can be referred to as the F1 interface.

[0039] A centralized unit (CU) may be connected to one or more distributed units (DUs) and may be responsible for functions at a higher layer than the distributed units (DUs). For example, the CU may be responsible for functions at the radio resource control (RRC) and packet data convergence protocol (PDCP) layers, while the DU and RU may be responsible for functions at lower layers. The DU may perform some functions (high PHY) of the radio link control (RLC), media access control (MAC), and physical (PHY) layers, while the RU may be responsible for the remaining functions (low PHY) of the PHY layer. In addition, for example, a digital unit (DU) may be included in a distributed unit (DU) depending on the implementation of a distributed deployment of the base station. Hereinafter, unless otherwise defined, the operations of DU (digital unit) and RU are described, but various embodiments of the present disclosure can be applied to both a base station arrangement including a CU and an arrangement in which the DU is directly connected to the core network (i.e., a base station in which the CU and DU are integrated into one entity (e.g., an NG-RAN node)).

[0040] Figure 3 illustrates an example of an electronic device that converts power supplied from an external source.

[0041] For example, the electronic device (300) of FIG. 3 may be an example of the base station (110) of FIG. 1, the DU (210) of FIG. 2, or the RU (220) of FIG. 2. However, the embodiments of the present disclosure are not limited thereto. For example, the electronic device (300) may include a massive multiple-input multiple-output unit (MMU). For example, the electronic device (300) may represent an example of communication equipment that obtains a voltage of a specific range from the outside, converts the obtained voltage, and uses the converted voltage. For example, the communication equipment may include a server (or server device).

[0042] For example, the MMU may be an electronic device that includes at least some of the functions of the DU (210) and the functions of the RU (220). For example, the RU (220) may perform amplification and radiation on a digital signal processed from the DU (210). For example, the MMU may perform processing on a digital signal obtained from the DU (210) and amplification and radiation on the processed signal. For example, the MMU may include a greater number of antenna elements than the RU (220). For example, the RU (220) may include four antenna elements (or 4T4R (4transmission 4reception)) or eight antenna elements (or 8T8R). The MMU may include 32 antenna elements (or 32T32R) or 64 antenna elements (or 64T64R). However, the present disclosure is not limited thereto. For example, the number of antenna elements included in the RU (220) and the number of antenna elements included in the MMU may be changed. Since the power consumption of each antenna element is relatively low compared to the RU (220), the MMU can operate a greater number of antenna elements than the RU (220). Hereinafter, for the convenience of explanation, an example in which the electronic device (300) is the MMU or the RU (220) is described, but the present disclosure is not limited thereto.

[0043] Referring to FIG. 3, an electronic device (300) may be connected to a bus (350). For example, the bus (350) may represent a structure or component for supplying power to a plurality of electronic devices (300, 370). For example, the bus (350) may be implemented as a line. In FIG. 3, two electronic devices (300, 370) are illustrated as being connected to the bus (350), but the present disclosure is not limited thereto. For example, the bus (350) may be connected to one electronic device or to three or more electronic devices.

[0044] For example, the power supplied by the bus (350) may include a voltage. For example, the power may be a DC voltage within a specific range. For example, the specific range may include -36 V (voltage) to -60 V. The above examples are merely exemplary for convenience of explanation, and the present disclosure is not limited thereto. For example, the specific range may be defined by a business operator using the electronic device (300) and the bus (350). In other words, the bus (350) may be designed to provide the specific range while taking into account the fact that the power used by each business operator may vary.

[0045] According to one embodiment, the electronic device (300) may include a power circuit (310), a control circuit (320), and an RF (radio frequency) component (330). In FIG. 3, a case where there is one RF component (330) connected to the power circuit (310) is illustrated, but the present disclosure is not limited thereto. For example, the electronic device (300) may include a plurality of RF components connected to the power circuit (310). In addition, in FIG. 3, as described above, when the electronic device (300) is the MMU or the RU (220), the electronic component connected to the power circuit (310) is the RF component (330), but the present disclosure is not limited thereto. For example, the electronic device (300) may include an electronic component connected to the power circuit (310) and for utilizing power provided from the power circuit (310).

[0046] According to one embodiment, the power circuit (310) of the electronic device (300) may include a DC-DC converter. For example, the DC-DC converter may use the DC voltage obtained from the bus (350) as an input voltage and convert the input voltage into a voltage (or output voltage) used by the RF component (330). In other words, the DC-DC converter may output the output voltage converted from the DC voltage obtained from the bus (350). For example, the output voltage may include a specific voltage (e.g., -48 V) that can be used by the RF component (330). For example, the DC-DC converter of the power circuit (310) may be referred to as an isolated bus converter or a resonant converter. For example, the resonant converter may include an LLC converter or a cap-isolation converter.

[0047] For example, the DC-DC converter may have a primary (1 stage) structure to generate the output voltage from the input voltage obtained from the bus (350). A specific example of the DC-DC converter having a primary structure is described below in FIG. 4a. Alternatively, the DC-DC converter may have a secondary (2 stage) structure to generate the output voltage from the input voltage obtained from the bus (350). A specific example of the DC-DC converter having a secondary structure is described below in FIG. 4b.

[0048] In the above example, the power circuit (310) is described as including the DC-DC converter, but the present disclosure is not limited thereto. For example, the power circuit (310) may include components for controlling power in addition to the DC-DC converter.

[0049] According to one embodiment, the electronic device (300) may include a control circuit (320) for controlling a power circuit (310). For example, the control circuit (320) may generate a signal for controlling the operation of the power circuit (310). For example, the control circuit (320) may include a pulse width modulation (PWM) controller or a pulse frequency modulation (PFM) controller. For example, when the control circuit (320) is the PWM controller, the signal may be referred to as a PWM signal. A specific example of the control circuit (320) as the PWM controller and the PWM signal generated (or output) from the control circuit (320) is described below in FIG. 5A. For example, when the control circuit (320) is the PFM controller, the signal may be referred to as a PFM signal. A specific example of the control circuit (320) which is the PFM controller and the PFM signal generated (or output) from the control circuit (320) is described below in FIG. 5b.

[0050] For example, the control circuit (320) can cause the operation of the power circuit (310) by providing the signal to the power circuit (310). For example, when the power circuit (310) is the DC-DC converter, the signal can be provided (or input) to a gate of a transistor of the DC-DC converter. For example, by providing the signal to the gate in the transistor of the DC-DC converter, the time for which the gate is driven can be controlled. The transistor can include a field effect transistor (FET). However, the present disclosure is not limited thereto.

[0051] According to one embodiment, the RF component (330) of the electronic device (300) may include at least one of a power amplifier, an RF integrated circuit (RFIC), or a transceiver (e.g., an RF front end, a radiator (or antenna element)). However, the present disclosure is not limited thereto. The RF component (330) may represent an electronic component that utilizes the output voltage provided from the power circuit (310).

[0052] As described above, since the input voltage acquired by the electronic device (300) may vary depending on the business operator, the specific range of input voltage that the power circuit (310) can convert may be designed taking into account a margin. For example, when using an emergency battery or a power outage battery in the event of a power outage, the electronic device (300) needs to operate normally even if a low input voltage (e.g., -36 V) is used. Therefore, the electronic device (300) requires a power circuit (310) that has a wide input range and can maintain high conversion efficiency even at low inputs.

[0053] In addition, the electronic device (300) requires a power circuit (310) that satisfies the minimum insulation condition. As described above, the power circuit (310) uses a low DC voltage of 100 V or less as input, but a rectifier may be required to convert an AC voltage obtained from an external source into the DC voltage. At this time, in order to ensure compatibility between the electronic device (300) and the rectifier, a power circuit (310) that satisfies the minimum insulation condition is required. For example, the minimum insulation condition may represent a functional isolation condition, which is an insulation standard with the rectifier, and an insulation condition of 1 kV or more. A DC-DC converter having a primary or secondary structure designed in consideration of the insulation standard is described in detail below with reference to FIGS. 4A and 4B.

[0054] Figures 4a and 4b illustrate examples of DC (direct current)-DC converters in electronic devices.

[0055] FIG. 4a illustrates an example in which the power circuit (310) in the electronic device (300) of FIG. 3 is a DC-DC converter having a primary structure. FIG. 4b illustrates an example in which the power circuit (310) in the electronic device (300) of FIG. 3 is a DC-DC converter having a secondary structure.

[0056] Referring to FIG. 4A, the electronic device (300) may include DC-DC converters (400) having a primary structure. For example, the electronic device (300) may include a DC-DC converter (410) for a first RF component, a DC-DC converter (420) for a second RF component, and a DC-DC converter (430) for a third RF component. The DC-DC converters illustrated in FIG. 4A are merely for convenience of explanation, and the present disclosure is not limited thereto. For example, the components included in each of the DC-DC converters (400), the arrangement of the components, the number of the components, and the number of the DC-DC converters (400) may be changed.

[0057] Referring to Figure 4a, the DC-DC converter (410) converts the input voltage (405) of the power source into an output resistance (R o ) may include a transformer for converting the output voltage (415) applied to the first portion (411) and the second portion (412). For example, the transformer may include a first portion (411) and a second portion (412). For example, the first portion (411) may be referred to as an input portion or input part. For example, the second portion (412) may be referred to as an output portion or output part. For example, the turns ratio (N) between the first portion (411) and the second portion (412) P : N S ), an output voltage (415) converted from the input voltage (405) can be determined. For example, the output voltage (415) can be input (or transmitted) to the first RF component (e.g., the first power amplifier (AMP_A)).

[0058] As described above, the description of the DC-DC converter (410) can be substantially equally applied to the DC-DC converter (420) for the second RF component (e.g., the second power amplifier (AMP_B)) or the DC-DC converter (430) for the third RF component (e.g., the transceiver (TRX)). The same description is omitted hereinafter.

[0059] As described above, an electronic device (300) including DC-DC converters (400) having a primary structure designed to satisfy an insulation condition can output relatively high efficiency with a relatively simple structure. However, an electronic device (300), such as the RU (220) or the MMU, requires a high-capacity power design, and DC-DC converters (400) designed in parallel may be used due to stress limitations (or allowable voltages) of elements within the DC-DC converter while supplying the high-capacity power. When the electronic device (300) includes DC-DC converters (400), since each DC-DC converter includes a transformer, the size of the electronic device (300) (or the power circuit (310)) may increase and the production cost may increase. In addition, since the electronic device (300) (or power circuit (310)) has a primary signal and a secondary signal to implement the off sequence required by the system, the size of the electronic device (300) (or power circuit (310)) may increase. To solve the problem described above, the electronic device (300) may utilize a DC-DC converter having a secondary structure. For specific details related thereto, reference may be made to FIG. 4B below.

[0060] Referring to FIG. 4B, the electronic device (300) may include a DC-DC converter (450) having a secondary structure. For example, the DC-DC converter (450) of the electronic device (300) may include a primary circuit (460) including a transformer for providing output voltages to a first circuit (470), a second circuit (480), and a third circuit (490), and a secondary circuit including the first circuit (470), the second circuit (480), and the third circuit (490). For example, the secondary circuit may include a first circuit (470) for a first RF component, a second circuit (480) for a second RF component, and a third circuit (490) for a third RF component. The DC-DC converter (450) illustrated in FIG. 4B is merely for convenience of description, and the present disclosure is not limited thereto. For example, the components included in the DC-DC converter (450), the arrangement of the components, the number of the components, and the number of DC-DC converters (400) may be changed.

[0061] Referring to Fig. 4b, the primary circuit (460) of the DC-DC converter (450) supplies the input voltage (455) of the power source to a capacitor (C Bus ) may include a transformer for converting the output voltage (465) applied to the first portion (461) and the second portion (462). For example, the transformer may include a first portion (461) and a second portion (462). For example, the first portion (461) may be referred to as an input portion or input part. For example, the second portion (462) may be referred to as an output portion or output part. For example, the turns ratio (N) between the first portion (461) and the second portion (462) P : N S), an output voltage (455) converted from an input voltage (455) can be determined. For example, the output voltage (465) can be input (or transmitted) to the first RF component (e.g., the first power amplifier (AMP_A)) through the first circuit (470), input (or transmitted) to the second RF component (e.g., the second power amplifier (AMP_B)) through the second circuit (480), and input (or transmitted) to the third RF component (e.g., the transceiver (TRX)) through the third circuit (490).

[0062] As described above, the electronic device (300) (or power circuit (310)) uses a DC-DC converter (450) including a primary circuit (460) for converting an input voltage (455) and a secondary circuit for distributing an output voltage (465), thereby satisfying the insulation condition and reducing the size of the electronic device (300) (or power circuit (310)) and reducing the production cost.

[0063] Non-isolated converters can use dedicated analog ICs to control the non-isolated converter. However, in the case of isolated bus converters, various modifications are required to meet user requirements due to relatively few applications (or usage environments) and relatively simple control structures, and therefore, dedicated analog ICs suitable for the isolated bus converter may be rare. In addition, existing dedicated analog ICs use a PWM-based duty control method. When controlling the isolated bus converter using the PWM method, voltage and current stresses on the components within the isolated bus converter may increase due to the wide input range and full power range covered. Accordingly, the advantages of the isolated bus converter implemented with a secondary structure (e.g., the DC-DC converter (450) of FIG. 4b) are lost. In addition, if the isolated bus converter is a resonant bus converter that utilizes resonance between a series capacitor and an inductor, a PFM method of control rather than a PWM-based duty control method may be required. For specific details on PWM-based control and PFM-based control, reference may be made to FIGS. 5a and 5b below.

[0064] Fig. 5a illustrates an example of a pulse width modulation (PWM) controller for controlling a DC-DC converter and an output signal of the PWM controller. Fig. 5b illustrates an example of a pulse frequency modulation (PFM) controller for controlling a DC-DC converter and an output signal of the PFM controller.

[0065] FIG. 5A illustrates an example of a plurality of pins included in a PWM controller (500), an example (510) of a PWM signal generated from a PWM controller (500) in a transient state section of the PWM controller (500), and an example (520) of a PWM signal generated from a PWM controller (500) in a steady state section of the PWM controller (500).

[0066] For example, the transient state section may represent a section different from the steady state section (or a section before reaching the steady state section). For example, the transient state section may include a start-up section. For example, the start-up section may include the timing at which the PWM controller (500) begins to generate and output a PWM signal. For example, the start-up section may be referred to as a start section.

[0067] Referring to FIG. 5A, the PWM controller (500) may include a plurality of pins (501, 502, 503, 504, 505, 506, 507, 508). In FIG. 5A, the PWM controller (500) is illustrated as including eight pins (501, 502, 503, 504, 505, 506, 507, 508), but the present disclosure is not limited thereto. For example, the PWM controller (500) may include seven or fewer pins, or nine or more pins. For example, the pins may be referred to as ports, nodes, or nodes. Alternatively, for example, the arrangement of pins included in the PWM controller (500) may be changed.

[0068] For example, the PWM controller (500) provides a driving voltage (V) for driving the PWM controller (500). DD) may include a pin (508) providing a ground for the PWM controller (500), and a pin (505) providing a ground for the PWM controller (500). For example, the PWM controller (500) may include a plurality of output pins (506, 507). However, the present disclosure is not limited thereto. For example, the PWM controller (500) may include one output pin.

[0069] For example, the PWM controller (500) may include a pin (501) for gradually increasing the duty of output PWM signals within a designated period. For example, the designated period may be included in the start-up period. For example, the operation of gradually increasing the duty within the start-up period may be referred to as a soft start (SS) (SS function). For example, the pin (501) may be referred to as a control pin, a duty pin, or an SS pin.

[0070] For example, the PWM controller (500) may include a pin (502) for adjusting the dead-time between PWM signals (OUTA, OUTB) output from each of the output pins (506, 507). For example, the pin (502) may be referred to as an RTD pin or a dead-time pin.

[0071] For example, the PWM controller (500) may include a pin (503) for sensing current for over current protection (OCP). For example, the pin (503) of the PWM controller (500) may be used to sense current passing through an input power supply of a DC-DC converter (e.g., DC-DC converter (450) of FIG. 4B) connected to the PWM controller (500). For example, the pin (503) may be referred to as a current sensing pin or a CS pin.

[0072] For example, the PWM controller (500) may include a pin (504) for adjusting the switching frequency (or driving frequency) of each of the PWM signals (OUTA, OUTB) output from each of the output pins (506, 507). For example, a lumped element (or passive element) connected to the pin (504) of the PWM controller (500) may be used to determine the operating frequency of each of the PWM signals in the steady-state period of the PWM controller (500). For example, the lumped element may include at least one of a resistor or a capacitor. For example, pin (504) may be referred to as a CT pin (e.g., when the lumped element connected to pin (504) is a capacitor), an RT pin (e.g., when the lumped element connected to pin (504) is a resistor), a CT / RT pin (e.g., when the lumped element connected to pin (504) is a capacitor and a resistor), or an operating frequency pin. For example, when the lumped element is a capacitor, the capacitor may include a multilayer ceramic capacitor (MLCC).

[0073] Referring to example (510), the PWM controller (500) can gradually increase the duty of each of the output PWM signals within the start-up period. For example, the PWM signal (OUTA) can have a first value indicating ON during a period (511a) according to the first duty within the cycle (511). The PWM signal (OUTA) can have a second value indicating OFF during a period other than the period (511a) according to the first duty within the cycle (511). For example, the PWM signal (OUTB) can have the first value indicating ON during a period (512a) according to the first duty within the cycle (512). The PWM signal (OUTB) can have the second value indicating OFF during a period other than the period (512a) according to the first duty within the cycle (512). Thereafter, the PWM signal (OUTA) may have the first value indicating ON during a section (513a) according to a second duty having a value greater than the first duty within the cycle (513). The PWM signal (OUTA) may have the second value indicating OFF during a section other than the section (513a) according to the second duty within the cycle (513). For example, each of the first duty and the second duty may be adjusted according to the capacitance of the capacitor connected to the pin (501). In other words, the PMW controller (500) may gradually increase the duty within the start-up section so that the duty ratio becomes about 1:1 (or 50%) according to the capacitance of the capacitor connected to the pin (501).

[0074] Referring to example (520), the PWM controller (500) can determine the operating frequency within the steady-state section by using a capacitor (e.g., the MLCC) connected to pin (504). For example, the PWM controller (500) can generate and output a PWM signal (OUTA) at a period (521) and a PWM signal (OUTB) at a period (522) according to the operating frequency. For example, in the steady-state section, an interval (525) between consecutive PWM signals (OUTA) and PWM signals (OUTB) can be referred to as a dead-time. For example, the interval (525) can be determined according to an RTD value determined based on pin (502).

[0075] When controlling a resonant bus converter, which is a DC-DC converter, through a PWM controller (500) based on a PWM method, the available operating frequency (or the operating frequency within the steady-state section) may be limited. At this time, since the resonant bus converter has a very small inductance of the series inductor, a relatively large inrush current in the start-up section may cause relatively large stress to be applied to the components within the resonant bus converter. In addition, when used in communication equipment requiring a wide input voltage range (e.g., -36 V to -60 V), since the DC-DC converter is designed based on the OCP level (or reference value) for a relatively low voltage (e.g., -36 V), the OCP level (or reference value) for a relatively high voltage (e.g., -60 V) may increase, thereby increasing the stress on the components within the DC-DC converter. Additionally, the PWM controller (500) supports auto recovery (or hiccup function), but there may be a disadvantage in that the OCP does not operate during the start-up period (or soft start period).

[0076] FIG. 5b illustrates an example of a plurality of pins included in a PFM controller (550), an example (560) of a PFM signal generated from a PFM controller (550) in a transient state section of the PFM controller (550), and an example (570) of a PFM signal generated from a PFM controller (550) in a steady state section of the PFM controller (550).

[0077] For example, the transient state period may represent a period different from the steady state period (or a period before reaching the steady state period). For example, the transient state period may include a start-up period. For example, the start-up period may include the timing at which the PFM controller (550) begins to generate and output a PFM signal. For example, the start-up period may be referred to as a start period.

[0078] Referring to FIG. 5B, the PFM controller (550) may include a plurality of pins (551, 552, 553, 554, 555, 556, 557, 558). In FIG. 5A, the PFM controller (550) is illustrated as including eight pins (551, 552, 553, 554, 555, 556, 557, 558), but the present disclosure is not limited thereto. For example, the PFM controller (550) may include seven or fewer pins, or nine or more pins. For example, the pins may be referred to as ports, nodes, or nodes. Alternatively, for example, the arrangement of pins included in the PFM controller (550) may be changed.

[0079] For example, the PFM controller (550) provides a driving voltage (V) for driving the PFM controller (550). DD) may include a pin (557) providing a ground for the PFM controller (550), and a pin (556) providing a ground for the PFM controller (550). For example, the PFM controller (550) may include a plurality of output pins (555, 558). However, the present disclosure is not limited thereto. For example, the PFM controller (550) may include one output pin.

[0080] For example, the PFM controller (500) may include a pin (501) for adjusting the dead-time between PFM signals (OUTA, OUTB) output from each of the output pins (555, 558). For example, the pin (501) may be referred to as a DT pin or a dead-time pin.

[0081] For example, the PFM controller (550) may include a pin (552) for adjusting the operating frequency (switching frequency) of each of the PFM signals (OUTA, OUTB) output from each of the output pins (555, 558). For example, a lumped element (or passive element) connected to a pin (554) of the PFM controller (550) may be used to determine the operating frequency of each of the PFM signals. Unlike the PWM controller (500), the PFM controller (550) may change the operating frequency even outside the steady-state range. For example, the lumped element may include at least one of a resistor or a capacitor. For example, the pin (552) may be referred to as an RT pin or an operating frequency pin.

[0082] For example, the PFM controller (550) may include a pin (553) for sensing current for over current protection (OCP). For example, the pin (553) of the PFM controller (550) may be used to sense current passing through an input power supply of a DC-DC converter (e.g., DC-DC converter (450) of FIG. 4B) connected to the PFM controller (550). For example, the pin (553) may be referred to as a current sensing pin or an OC pin.

[0083] For example, the PFM controller (550) may include a pin (554) for gradually increasing the duty of the output PFM signals within a designated period. For example, the designated period may be included in the start-up period. For example, the operation of gradually increasing the duty within the start-up period may be referred to as a soft start (SS) (or SS function). For example, the pin (554) may be referred to as a control pin, a duty pin, or an SS pin.

[0084] Referring to example (560), the PFM controller (550) can gradually increase the operating frequency of each of the output PFM signals within the start-up period. For example, the operating frequency can be inversely proportional to the period. For example, the PFM signal (OUTA) can have a first value indicating ON during a period (561) according to a first period. For example, the PFM signal (OUTA) can have the first value indicating ON during a period (563) according to a second period following the first period. For example, the length of the second period can be longer than the length of the first period. For example, the PFM signal (OUTA) can have the first value indicating ON during a period (565) according to a third period following the second period. For example, the length of the third period can be longer than the length of the second period. For example, the PFM signal (OUTB) may have the first value indicating ON during a period (562) according to a fourth period corresponding to the first period. The fourth period may represent a period of OUTB having a length corresponding to the length of the first period of OUTA. Referring to example (560), the PFM controller (550) may gradually increase the period of each of the output PFM signals, and at this time, the duty of each of the PFM signals may be fixed. For example, the duty ratio may be 1:1 (or 50%).

[0085] Referring to example (570), the PFM controller (550) can generate and output a signal having the lowest operating frequency (or the longest period) within the above-described normal state interval. For example, the PFM controller (550) can generate and output a PFM signal (OUTA) at a period (571) and a PFM signal (OUTB) at a period (572) according to the above-described operating frequency.

[0086] When using a PFM controller (550), regulation of the output may be possible, albeit within a narrow range, when connected to feedback. In addition, the PFM controller (550) can change the frequency within the start-up period, but since it is used for an AC (alternating current)-DC converter, the range of the operating frequency that can be changed is limited, and the range cannot be changed depending on the system. Accordingly, it is practically impossible to provide a relatively high operating frequency required in the start-up period, and even if the PFM controller (550) is used, a relatively large inrush current may be generated. In addition, the operating frequency within the steady-state period may be designed to be limited (e.g., less than 150 kHz) depending on the range of the operating frequency in the start-up period. Similar to the PWM controller (500), the stress on the components of the converter connected to the PFM controller (550) may increase at a relatively high voltage due to the OCP level that is independent of the input voltage. The resonant PFM controller, which provides high frequencies, is not a dedicated circuit for bus converters, and thus may increase production costs due to additional functions for the bus converter or functions that are not used. Furthermore, as described above, the PFM controller (550) is designed for AC-DC converters, and thus a PFM controller (550) for communication equipment and resonant bus converters is required.

[0087] Referring to the above, analog control circuits for an insulated bus converter may include a PWM controller (500). When a resonant bus converter is used among the insulated bus converters, PFM control of the PFM controller (550) may be required in at least some sections (e.g., the start-up section). When the resonant bus converter is used, the problems of the PWM controller (500) or the PFM controller (550) are as follows.

[0088] ① First, when using the resonant bus converter, a relatively large inrush current within the start-up period may be a problem. For example, when using the resonant bus converter, the input voltage may be entirely applied to the series inductor for resonance within the start-up period. Since the inductance of the series inductor in the resonant bus converter is relatively low, the inrush current within the start-up period may increase relatively significantly. The inrush current passing through the series inductor may be referred to as the following mathematical equation.

[0089]

[0090] Above i Lr,start is the series inductor (e.g., L in Fig. 4b) in the resonant bus converter. R ) the inrush current passing through the V in is the input voltage of the resonant bus converter, and V Cr is a series capacitor (e.g., C in Fig. 4b) that resonates with the series inductor in the resonant bus converter. R ), the above V o is the output voltage of the resonant bus converter (e.g., C in Fig. 4b). Bus ) the voltage applied to the D, the duty of the signal (e.g., PWM signal) for controlling the transistors of the resonant bus converter, and the T s can represent a period which is the reciprocal of the operating frequency of the above signal.

[0091] Referring to the mathematical formula described above, the L r is the inductance of the above series inductor and the V inis an input voltage obtained from outside the resonant bus converter, and may have a fixed value during design. Accordingly, as the magnitude of the operating frequency of the signal for controlling the transistors increases (or the period becomes shorter), the inrush current may decrease. Accordingly, the controller for controlling the resonant bus converter needs to perform an operation of initially driving at a relatively high frequency within the start-up period and then changing to a relatively low frequency as it progresses to the steady-state period.

[0092] For example, the stress of the electronic device (300) may include the stress of transistors operating as switches within a DC-DC converter. For example, each of the transistors may include a resistor and a capacitor connected in parallel therein. If excessive current passes through the resistor, the transistors may be damaged by the stress caused by the excessive current. For example, the magnitude of the current may be related to the magnitude of the inrush current. By reducing the magnitude of the inrush current within the start-up period, the stress of the transistors may be reduced.

[0093] For example, it is assumed that the resonant bus converter transmits at least 1 kW of power. Considering the stress of the elements within the resonant bus converter, an operating frequency of at least 500 kHz and at most 1 MHz is required within the start-up period. When the PWM controller (500) is used, the operating frequency is fixed, so when the operating frequency is increased within the start-up period, the operating frequency after the start-up period cannot be changed to have an appropriate frequency for the steady-state period. In addition, when the PFM controller (550) is used, the operating frequency must be variable to have a frequency of about 500 kHz or more within the start-up period, but the variable range of the PFM controller (550) may be limited.

[0094] ② Second, when using the resonant bus converter, the controller (e.g., PWM controller (500) or PFM controller (550)) may have a high OCP level. Since the controller has one fixed level of OCP, considering the characteristics of a system having a wide input voltage range (e.g., -36 V to -60 V), an OCP level needs to be set based on a low input voltage. For example, when the power used by the resonant bus converter is 1000 W, the magnitude of the current passing through the input power supply at a low input voltage (e.g., -36 V) may be about 27 A, and the magnitude of the current may be about 16 A at a high input voltage (e.g., -60 V). Since the OCP level is detected (or sensed) using the magnitude of the current passing through the input power supply, the OCP level may be set to a value based on 27 A. Accordingly, when the same OCP level is used at a relatively high input voltage as at a relatively low input voltage, the current-dependent OCP may be operated at a point with relatively high power (e.g., 60*27=approximately 1620W). Therefore, when the OCP is operated (or abnormal operation is performed) while using a relatively high input voltage, the stress on the components within the resonant bus converter may increase, and the possibility of damage may increase. Therefore, the OCP level of the controller needs to be adjusted in consideration of the input voltage of the resonant bus converter.

[0095] ③ The third problem may be related to the controller (e.g., PWM controller (500) or PFM controller (550)) turning off the operation during OCP operation and performing a hiccup function (or mode) for automatic recovery. For example, the hiccup function may include periodically attempting to restart (or turn on). When using the resonant bus converter, even when attempting the restart, a relatively high operating frequency may be required in consideration of the inrush current. At this time, a circuit that resets (or refreshes) the operating frequency so that it can be changed to the high frequency may be required. Referring to the above mathematical expression 1, when the magnitude of the input voltage used at the initial start is relatively small, the inrush current may be lowered. However, when a restart is performed by the automatic recovery after a fault (or fault state) of the controller occurs, the magnitude of the input voltage may have a relatively high value, which may increase the inrush current. For example, the fault may include a case where a current exceeding the OCP level is sensed or a short of some components is detected. Therefore, even in the case of the restart, in order to lower the inrush current, it is necessary to set the operating frequency of the signal generated and output from the controller to a high frequency.

[0096] ④ The fourth problem may be related to the second problem. For example, a circuit is required to reduce the stress on the components (e.g., transistors) within the resonant bus converter while the controller (e.g., PWM controller (500) or PFM controller (550)) performs the hiccup function when a fault occurs (or in a fault state). For example, if the controller restarts (or starts a start-up period) while performing the hiccup function, the controller may perform the hiccup function until the fault is resolved. However, since a signal for driving the components is provided according to the hiccup function, the components may be temporarily operated. Accordingly, current may pass through the components, which may apply additional stress. Therefore, in order to prevent secondary damage (burnt) of the resonant bus converter, a circuit may be required to limit the inrush current during the restart operation according to the automatic recovery after the fault.

[0097] ⑤ Finally, when there is no power required by the system including the resonant bus converter or in idle mode, the output voltage of the resonant bus converter may increase without regulation. The resonant bus converter can generate an output voltage from an input voltage at a fixed frequency in a steady state without receiving a separate feedback signal, and transmit the output voltage to an application part within the system (e.g., an RF component (330) of FIG. 3). At this time, the output voltage may increase without regulation due to parasitic components (e.g., parasitic capacitance) seen in the rectifier stage for the output. To regulate the output voltage, a method of adding a dummy load or performing a hiccup function at a low load is used, but this has the disadvantages of low efficiency and slow response speed. Considering the characteristics of electronic devices (e.g., communication equipment) that require a relatively long idle mode operation time and fast response speed, a solution capable of high-efficiency no-load regulation without increasing the output voltage may be required.

[0098] Hereinafter, the present disclosure proposes a PWM circuit for controlling an isolated bus converter (e.g., a resonant bus converter) for communication equipment (e.g., an RU or MMU). The isolated bus converter has a useful and simple topology in terms of circuitry, but has the problems described above. The present disclosure can provide solutions for resolving the problems described above by utilizing simple signal level processing of a circuit (e.g., an analog IC) with low production cost and small size. Although it can be implemented with a digital IC, the digital IC has a relatively high production cost, and the circuit configuration for driving the digital IC can be complex. In addition, the digital IC may further increase the production cost because it additionally requires a separate fusing (e.g., flash fusing) or firmware downloading task.

[0099] The control circuit according to the present disclosure and the electronic device including the same can use a PWM controller (e.g., PWM controller (500)) and an additional circuit connected to the PWM controller or an additional circuit in a DC-DC converter connected to the PWM controller. The control circuit according to the present disclosure and the electronic device including the same can use a PWM controller (e.g., PWM controller (500)) in which PFM control is implemented so as to perform modulation of the operating frequency within the start-up period by adding the additional circuit. In addition, the control circuit according to the present disclosure and the electronic device including the same can reduce stress on components in a DC-DC converter in which the PWM controller is used by adding the additional circuit. Accordingly, the control circuit according to the present disclosure and the electronic device including the same can reduce production costs and reduce the size of the electronic device by using the additional circuit having a relatively simple configuration.

[0100] Fig. 6 illustrates an example of a control circuit including a switching circuit for adjusting the operating frequency (switching frequency) of an output signal of a PWM controller.

[0101] The control circuit (600) of FIG. 6 may be an example of the control circuit (320) of FIG. 3. For example, the control circuit (600) may be connected to the power circuit (310) of FIG. 3. For example, the power circuit (310) may include a DC-DC converter, which is a resonant bus converter. For example, the control circuit (600) may be connected to a gate of a transistor of the DC-DC converter. For example, the control circuit (600) may generate a signal and control the operation of the transistor (or the gate) through the generated signal. For example, the signal may be referred to as a PWM signal.

[0102] Referring to FIG. 6, the control circuit (600) may include a PWM controller (500), a lumped element (605), and a switching circuit (610). For example, the control circuit (600) may include the PWM controller (500) of FIG. 5A. For example, the PWM controller (500) of the control circuit (600) may include at least some of the plurality of pins included in the controller (500) of FIG. 5A. In FIG. 6, for convenience of explanation, the PWM controller (500) is illustrated as including pins (504) and pins (508), but the embodiments of the present disclosure are not limited thereto. For example, pin (504) may be an adjustment pin for adjusting an operating frequency of a signal (or PWM signal) output from the PWM controller (500).

[0103] In one embodiment, the lumped element (605) may be connected to the pin (504). For example, the lumped element (605) may be connected to the pin (504) through a node (610a). For example, the lumped element (605) may include at least one of a resistor or a capacitor. For example, within a steady-state period, the operating frequency of the PWM signal may be adjusted (or determined) according to the element value of the lumped element (605) connected to the pin (504). For example, when the lumped element (605) is a resistor, the element value may be resistance. For example, when the lumped element (605) is a capacitor, the element value may be capacitance. In one embodiment, the switching circuit (610) may be connected to the pin (504). For example, the switching circuit (610) may be connected to the pin (504) through a node (610a).

[0104] According to one embodiment, the switching circuit (610) comprises a first resistor (611) (R inrush ), diode (612), capacitor (613) (C inrush ), and the second resistor (614) (R dis ) may be included. For example, the first resistor (611) (R inrush ) driving voltage (V) of PWM controller (500) DD ) may be applied. According to one embodiment, the diode (612) comprises a first resistor (611) (R inrush ), capacitor (613) (C inrush ), and the second resistor (614) (R dis ) can be connected to each other. For example, the first resistor (611) (R inrush ) can be connected to the anode of the diode (612). For example, the capacitor (613) (C inrush ) and the second resistor (614) (R dis) can each be connected to the cathode of the diode (612) through the node (610b). The capacitor (613) (C inrush ) and the second resistor (614) (R dis ) can be arranged in parallel. For example, capacitors (613) (C inrush ) and the second resistor (614) (R dis ) can be connected in parallel between the node (610a) connected to the pin (504) and the concentration element (605) and the node (610b) connected to the diode (612).

[0105] According to one embodiment, the switching circuit (610) may be used to adjust the driving frequency of the PWM signal within the start-up period of the PWM controller (500). Referring to the above, in the steady-state period, the driving frequency of the PWM signal may be determined based on the element value of the lumped element (605). For example, if the lumped element (605) is a capacitor (C CT ), the lumped element (605) can be charged by a current source located inside the pin (504). When the voltage applied to the lumped element (605) reaches a reference voltage, a triangle wave for generating a PWM signal can be generated by discharging the lumped element (605). At this time, the time taken to reach the reference voltage can be used to determine the operating frequency of the PWM signal. Accordingly, the switching circuit (610) can adjust the operating frequency of the PWM signal by adjusting the time taken for the voltage of the lumped element (605) to reach the reference voltage.

[0106] For example, within the above start-up period, the driving voltage (V DD ) is the first resistor (611) (R inrush ) is applied to the first resistor (611) (R inrush) can be additionally added to the concentration element (605). Accordingly, the voltage of the concentration element (605) can reach the reference voltage more quickly. Within the start-up period, the driving voltage (V DD ) is the first resistor (611) (R inrush ) as time passes before the above steady state period, the capacitor (613) (C inrush ) can gradually increase the voltage applied to the capacitor (613) (C inrush ) gradually increases, the first resistor (611) (R inrush ) can be gradually reduced. The voltage applied to the first resistor (611) (R inrush ) can also be reduced. For example, the length of the start-up section can be reduced by the first resistor (611) (R inrush ) and capacitor (613)(C inrush ) can be determined based on the time constant. For example, the capacitor (613) (C inrush ) is the driving voltage (V DD ) corresponds to the first resistor (611) (R inrush ) can be 0. As the current added to the lumped element (605) decreases, the operating frequency of the PWM signal can be determined by the lumped element (605). In other words, within the steady-state section, the operating frequency of the PWM signal can be adjusted based on the lumped element (605). The second resistor (614) (R dis ) is a capacitor (613) (C inrush ) can be used to discharge the residual voltage charged in the battery.

[0107] As described above, by connecting the switching circuit (610) to the pin (504) of the PWM controller (500), PFM-type control (change of operating frequency) can be implemented within the start-up period. Accordingly, the control circuit according to the present disclosure and the electronic device (300) including the same can provide a relatively high operating frequency within the start-up period and a relatively low operating frequency upon entering the steady-state period, even if the PWM controller (500) is used. By providing a relatively high operating frequency within the start-up period, the inrush current within the start-up period is lowered, and thus the stress on the components (e.g., transistors) of the DC-DC converter connected to the PWM controller (500) can be reduced.

[0108] In Fig. 6, the switching circuit (610) is arranged in parallel with the capacitor (613) (C inrush ) and the second resistor (614) (R dis ), but the present disclosure is not limited thereto. For example, the switching circuit (610) may be implemented through an inductor and a resistor arranged in series.

[0109] Fig. 7 illustrates an example of a control circuit including a voltage dividing circuit for adjusting the over current protection (OCP) level of a PWM controller.

[0110] The control circuit (700) of FIG. 7 may be an example of the control circuit (320) of FIG. 3. For example, the control circuit (700) may be connected to the power circuit (310) of FIG. 3. For example, the power circuit (310) may include a DC-DC converter, which is a resonant bus converter. For example, the control circuit (700) may be connected to a gate of a transistor of the DC-DC converter. For example, the control circuit (700) may generate a signal and control the operation of the transistor (or the gate) through the generated signal. For example, the signal may be referred to as a PWM signal.

[0111] Referring to FIG. 7, the control circuit (700) may include a PWM controller (500) and a voltage distribution circuit (710). For example, the control circuit (700) may include the PWM controller (500) of FIG. 5A. For example, the PWM controller (500) of the control circuit (700) may include at least some of the plurality of pins included in the controller (500) of FIG. 5A. In FIG. 7, for convenience of explanation, the PWM controller (500) is illustrated as including a pin (503), but the embodiments of the present disclosure are not limited thereto. For example, the pin (503) may represent a current sensing pin for sensing current for over current protection (OCP).

[0112] According to one embodiment, the voltage distribution circuit (710) supplies the input voltage (V) of the DC-DC converter in ) is the first distribution resistor (711) (R) up ), the second distribution resistor (712) (R) connected to the ground down ), and a third distribution resistor (713) (R) connected to pin (503). CS ) may be included. For example, the third distribution resistor (713) (R CS ) is a pin (503), a capacitor (705a) (C) connected to the pin (503)CS ), can be connected through a node (710a) and a component (705a) (e.g., a resistor) connected to the pin (503). For example, a first distribution resistor (711) (R up ), second distribution resistor (712) (R down ), and the third distribution resistor (713) (R CS ) can be connected to each other through nodes (710b).

[0113] According to one embodiment, the PWM controller (500) may perform an OCP operation when the level of voltage applied to the pin (503) exceeds a reference value. For example, when the current passing through the pin (503) (or the current sensed by the pin (503)) increases, the level of the voltage may exceed the reference value. For example, the OCP operation may include turning off the operation of the PWM controller (500).

[0114] According to one embodiment, the reference value has a fixed value, and the level of the voltage applied to the pin (503) is the input voltage (V in ) by changing it depending on the input voltage (V in ) can be relatively adjusted. For example, the input voltage (V) can be adjusted through a voltage distribution circuit (710). in ) voltage information can be applied to pin (503). For example, the voltage information may be an input voltage (V in ) may be a voltage distributed by a voltage distribution circuit (710). The voltage information applied to the pin (503) may be an input voltage (V in ) can be increased. In other words, the voltage information can be increased as the input voltage (V in ) can be proportional to the input voltage (V in) is relatively high (e.g., -60 V), the voltage information applied to the pin (503) increases, and the OCP operation of the PWM controller (500) can be performed by the current passing through the pin (503) having a relatively low value. Alternatively, the input voltage (V in ) is relatively low (e.g., -36 V), the voltage information applied to the pin (503) is reduced, and the OCP operation of the PWM controller (500) can be performed by the current passing through the pin (503) having a relatively high value.

[0115] Referring to the above, the control circuit (700) supplies the voltage applied to the pin (503) for current detection of the PWM controller (500) to the input voltage (V) through the voltage distribution circuit (710). in ) can be set to have a value dependent on the input voltage (V). For example, the voltage applied to the pin (503) can be referred to as a threshold voltage for the OCP. For example, the threshold voltage can be set to have a value dependent on the input voltage (V) by the voltage distribution circuit (710). in ) can be adjusted according to the input voltage (V in ), OCP operation can be performed at a low current level at a high input voltage, and OCP operation can be performed at a high current level at a low input voltage.

[0116] Referring to Fig. 7, a bias voltage can be formed at the pin (503) by the voltage distribution circuit (710). By performing gain adjustment of the current amplification circuit (hereinafter, power amplifier (955) of Fig. 9b) connected to the element (705b), the level of the bias voltage can be adjusted (or removed). In addition, the third distribution resistor (713) (R CS ), the level of the bias voltage can be adjusted based on the superposition.

[0117] In FIG. 7, the control circuit (710) is illustrated as including a voltage divider circuit (710) including three resistors, but the present disclosure is not limited thereto. For example, the control circuit (710) may also include a voltage divider circuit (710) including three capacitors. For example, the voltage divider circuit (710) of FIG. 7 is illustrated as including an input voltage (V in ) distribution and input voltage (V) to pin (503) in ) may include a configuration for providing voltage information.

[0118] Figure 8 illustrates an example of a control circuit including a discharging circuit of a capacitor for adjusting the operating frequency.

[0119] The control circuit (800) of FIG. 8 may be an example of the control circuit (320) of FIG. 3. For example, the control circuit (800) may be connected to the power circuit (310) of FIG. 3. For example, the power circuit (310) may include a DC-DC converter, which is a resonant bus converter. For example, the control circuit (800) may be connected to a gate of a transistor of the DC-DC converter. For example, the control circuit (800) may generate a signal and control the operation of the transistor (or the gate) through the generated signal. For example, the signal may be referred to as a PWM signal.

[0120] Referring to FIG. 8, the control circuit (800) may include a PWM controller (500), a switching circuit (610), and a discharge circuit (810). For example, the control circuit (800) may include the PWM controller (500) of FIG. 5A. For example, the PWM controller (500) of the control circuit (800) may include at least some of the plurality of pins included in the controller (500) of FIG. 5A. In FIG. 8, for convenience of explanation, the PWM controller (500) is illustrated as including pins (504) and pins (501), but the embodiments of the present disclosure are not limited thereto. For example, pin (504) may be an adjustment pin for adjusting an operating frequency of a signal (or PWM signal) output from the PWM controller (500). For example, pin (501) may represent a pin for gradually increasing the duty of PWM signals output from PWM controller (500). For example, the switching circuit (610) of the control circuit (800) may be an example of the switching circuit (610) of FIG. 6. Referring to FIG. 8, the PWM controller (500) of the control circuit (800) may be connected to the switching circuit (610) via pin (504).

[0121] According to one embodiment, the discharge circuit (810) of the control circuit (800) comprises a first transistor (811), a second transistor (812), and a discharge resistor (813) (R dis2 ) may be included.

[0122] For example, the first transistor (811) has a gate connected to the pin (501) via the node (810a), and a driving voltage (V) of the PWM controller (500). DD) may include a drain to which current is applied, and a source connected to the ground. For example, the gate of the first transistor (811) may be connected to a node (810a) through a device (e.g., a resistor) for inducing current. The device may be omitted. The node (810a) may include the gate of the first transistor (811), a duty capacitor (805a) (C SS ), and duty resistor (805b) (R SS ) may represent a node to which the first transistor (811) is connected. For example, the drain of the first transistor (811) may be connected to the gate of the second transistor (812) via the node (810b). For example, the source of the first transistor (811) may be connected to the source of the second transistor (812).

[0123] For example, the second transistor (812) is driven by a voltage (V DD ) is applied to the gate, discharge resistor (813) (R dis2 ) and a source connected to the ground. For example, the gate of the second transistor (812) may be connected to the drain of the first transistor (811) via the node (810b). For example, the source of the second transistor (812) may be connected to the source of the first transistor (811). For example, the drain of the second transistor (812) may be connected to the distribution resistor (813) (R dis2 ) can be connected to the switching circuit (610). For example, the distribution resistor (813) (R dis2 ) can connect the drain of the second transistor (812) and the node (610b) of the switching circuit (610).

[0124] The PWM controller (500) provides a soft start function within the start-up period by using a duty capacitor (805a) (C SS) can be charged through a current source inside the pin (501). The PWM controller (500) is a duty capacitor (805a) (C SS ) reaches the reference voltage, the soft start function can be stopped. After this, when the PWM controller (500) has a fault, the PWM controller (500) stops outputting (e.g., stops outputting the PWM signal or turns it OFF), and the duty capacitor (805a) (C SS ) can be discharged to another reference voltage. For example, the other reference voltage may be a voltage lower than the reference voltage. Duty capacitor (805a) (C SS ) is discharged to the above-mentioned other reference voltage, the duty capacitor (805a) (C) is discharged according to the automatic recovery operation. SS ) charging to the above reference voltage and discharging to the other reference voltage can be repeated.

[0125] According to one embodiment, within the start-up period of the PWM controller (500), the operating frequency of the PWM signal may be changed according to the switching circuit (610). For example, within the start-up period, the driving voltage (V DD ) within the switching circuit (610) by the capacitor (613) (C inrush ) is charged, the operating frequency may be reduced. After the start-up period, a restart may be performed as the fault of the PWM controller (500) is detected. During the start-up period, the driving voltage (V DD ) to correspond to the capacitor (613) (C inrush ) is already charged, the operating frequency having a high frequency cannot be used at the time of restart. Therefore, the capacitor (613) (C) of the switching circuit (610) at the time of the fault inrush ) may require discharge.

[0126] According to one embodiment, the discharge circuit (810) is configured to, when the PWM controller (500) has a fault, to supply a capacitor (613) (C inrush ) can be used for discharging. For example, the gate of the first transistor (811) of the discharge circuit (810) may be ON before the fault. The state of the gate of the first transistor (811) of the discharge circuit (810) may be changed from ON to OFF by the voltage of the pin (501) that decreases according to the fault. As the first transistor (811) turns OFF, the state of the second transistor (812) (or the gate of the second transistor (812)) may be changed from OFF to ON. The second transistor (812) may be changed to ON as the fault is detected and may be electrically connected to the switching circuit (610). In other words, as the second transistor (812) turns ON, the capacitor (613) (C) of the switching circuit (610) inrush ) and discharge resistance (813)(R dis2 ) is connected, and the capacitor (613) (C inrush ) is charged with the discharge resistance (813) (R dis2 ) can be consumed through the capacitor (613). After this, when the start-up period starts again, the second transistor (812) changes from ON to OFF, and the discharged capacitor (613) (C inrush ) can switch so that the operating frequency of the PWM signal has a high frequency. Switching so that the high frequency is present in the restarted start-up section can refer to the operations of FIG. 6 described above.

[0127] Although FIG. 8 illustrates that the control circuit (800) includes a discharge circuit (810) including two transistors of the npn type (e.g., a first transistor (811) and a second transistor (812)), the present disclosure is not limited thereto. For example, the control circuit (800) may also include a discharge circuit (810) including one transistor of the pnp type. For example, the transistor of the pnp type may perform substantially the same function (or operation) as the first transistor (811) and the second transistor (812).

[0128] Figures 9a and 9b illustrate examples of control circuits including a protection circuit.

[0129] The control circuit (900) of FIG. 9A may be an example of the control circuit (320) of FIG. 3. For example, the control circuit (900) may be connected to the power circuit (310) of FIG. 3. For example, the power circuit (310) may include a DC-DC converter, which is a resonant bus converter. For example, the control circuit (900) may be connected to a gate of a transistor of the DC-DC converter. For example, the control circuit (900) may generate a signal and control the operation of the transistor (or the gate) through the generated signal. For example, the signal may be referred to as a PWM signal.

[0130] Referring to FIG. 9A, the control circuit (900) may include a PWM controller (500) and a first protection circuit (910). For example, the control circuit (900) may include the PWM controller (500) of FIG. 5A. For example, the PWM controller (500) of the control circuit (900) may include at least some of the plurality of pins included in the controller (500) of FIG. 5A. In FIG. 9A, for convenience of explanation, the PWM controller (500) is illustrated as including a pin (501), but the embodiments of the present disclosure are not limited thereto. For example, the pin (504) may be an adjustment pin for adjusting an operating frequency of a signal (or PWM signal) output from the PWM controller (500). For example, the pin (501) may represent a pin for gradually increasing the duty of PWM signals output from the PWM controller (500).

[0131] According to one embodiment, the first protection circuit (910) of the control circuit (900) comprises a diode (911), a transistor (912), and a protection capacitor (913) (C SS2 ) may be included.

[0132] For example, the diode (911) of the first protection circuit (910) is connected to the gate and node (910a) of the transistor (912) and the cathode and protection capacitor (913) (C SS2 ) and the anode connected to the source of the transistor (912). For example, the node (910a) may include a diode (911), the gate of the transistor (912), and a duty capacitor (905a) (C SS ), and duty resistor (905b) (R SS ) can represent a node to which the duty capacitor (905a) (C SS ), and duty resistor (905b) (R SS ) is the duty capacitor (805a) (C) of Fig. 8 SS ), and duty resistor (805b) (R SS) can be understood as being virtually identical to it.

[0133] For example, the transistor (912) of the first protection circuit (910) has the gate connected to the cathode of the diode (911), the driving voltage (V) of the PWM controller (500) DD ) is applied to the drain, and the anode of the diode (911) and the protection capacitor (913) (C SS2 ) may include a source connected to the transistor (912). In Fig. 9a, the driving voltage (V DD ) is shown as an example in which the driving voltage (V DD ) may be applied with a voltage source having a specified value (e.g., 3.3 V).

[0134] According to one embodiment, the protection capacitor (913) (C) of the first protection circuit (910) SS2 ) can be charged while the voltage applied to the pin (501) increases according to the soft start function within the start-up period of the PWM controller (500). For example, while the voltage applied to the pin (501) increases, a voltage is applied to the gate of the transistor (912), thereby increasing the driving voltage (V DD ) by the protection capacitor (913)(C SS2 ) can be charged. According to one embodiment, while the PWM controller (500) is within the steady-state period, the voltage applied to the pin (501) is fixed to the reference voltage, and the protection capacitor (913) (C SS2 ) can stop charging. For example, the protective capacitor (913) (C) that stops the charging SS2 ) may be fully charged. According to one embodiment, when the voltage applied to the pin (501) is reduced in the event of a fault in the PWM controller (500), the protection capacitor (913) (C) is turned on through the diode (911). SS2) can be transferred to the pin (501). For example, when the voltage applied to the pin (501) decreases, the diode (911) can be conducted. Through the conducted diode (911), the protective capacitor (913) (C SS2 ) is transferred to the pin (501), the rate of decrease of the voltage applied to the pin (501) may be slowed down. For example, when the first protection circuit (910) is not used, it is assumed that the voltage applied to the pin (501) is decreased at the first rate. When the first protection circuit (910) is used, the protection capacitor (913) (C SS2 ) when the energy is transferred from the pin (501), the voltage applied to the pin (501) may be reduced to a second speed that is slower than the first speed. In order for the PWM controller (500) to perform start-up again, the voltage applied to the pin (501) needs to be changed to be lower than the other reference voltage. Therefore, the protection capacitor (913) (C) of the first protection circuit (910) SS2 ) can be used to slow down the rate of decrease of the voltage applied to the pin (501), thereby slowing down the cycle of automatic recovery.

[0135] As described above, when an element of the power circuit (310) including the DC-DC converter is damaged, an overcurrent may occur in the power circuit (310). To protect against this, a protection circuit providing an OCP operation (function) may be used. Damage to the element may occur when stress accumulates in the elements of the power circuit (310). Therefore, in order to reduce the stress, the frequency of occurrence of the stress may be reduced (or the cycle of automatic recovery may be increased) or the level of the stress may be reduced. For example, the first protection circuit (900) of FIG. 9A may reduce the stress by increasing the cycle of the automatic recovery.

[0136] The control circuit (950) of FIG. 9B may be an example of the control circuit (320) of FIG. 3. For example, the control circuit (950) may be connected to the power circuit (310) of FIG. 3. For example, the power circuit (310) may include a DC-DC converter, which is a resonant bus converter. For example, the control circuit (950) may be connected to a gate of a transistor of the DC-DC converter. For example, the control circuit (950) may generate a signal and control the operation of the transistor (or the gate) through the generated signal. For example, the signal may be referred to as a PWM signal.

[0137] Referring to FIG. 9B, the control circuit (950) may include a PWM controller (500), an operational amplifier (OP AMP) (955), and a second protection circuit (960). For example, the control circuit (950) may include the PWM controller (500) of FIG. 5A. For example, the PWM controller (500) of the control circuit (950) may include at least some of the plurality of pins included in the controller (500) of FIG. 5A. In FIG. 9B, for convenience of explanation, the PWM controller (500) is illustrated as including pins (501) and (503), but the embodiments of the present disclosure are not limited thereto. For example, pin (501) may represent a pin for gradually increasing the duty of PWM signals output from the PWM controller (500). For example, pin (503) may represent a current sensing pin for sensing current for over current protection (OCP). For example, operational amplifier (955) may include a differential amplifier.

[0138] According to one embodiment, the operational amplifier (955) may include a plurality of pins. For example, the operational amplifier (955) may include a plurality of input terminals (+in, -in), a plurality of voltage terminals (+V s , -V s ), and an output terminal (Out) (955b). For example, the plurality of input terminals may include an input terminal (955a) which is an input terminal. For example, an output resistor (957) (R) may be provided between the input terminal (955a) and the output terminal (955b) of the operational amplifier (955). diff_H2 ) can be placed. An input resistor (956) (R) is placed between the input terminal (955a) and the ground. diff_L2 ) can be placed.

[0139] According to one embodiment, the operational amplifier (955) may be connected to pin (503). For example, the output terminal (955b) of the operational amplifier (955) may be connected to pin (503) via element (705b).

[0140] According to one embodiment, the second protection circuit (960) may include a transistor (961) and a protection resistor (962). For example, the transistor (961) of the second protection circuit (960) may include a source connected to ground, a gate connected to a drain of a first transistor (811) of the discharge circuit (810), and a drain connected to a protection resistor (962).

[0141] According to one embodiment, the second protection circuit (960) may be placed between the operational amplifier (955) and the discharge circuit (810). For example, the gate of the transistor (961) of the second protection circuit (960) is connected to the drain of the first transistor (811) of the discharge circuit (810) via the node (810b), and the driving voltage (V) of the PWM controller (500) DD ) can be applied to the gate of the transistor (961). For example, the protection resistor (962) can be connected through the input terminal (955a) and the node (960a).

[0142] According to one embodiment, the PWM controller (500) can obtain current information of the input power of the DC-DC converter through the pin (503). For example, the operational amplifier (955) can generate the current information amplified by a gain from a value related to the current passing through the input power. For example, the gain can be an input resistance (956) (R diff_L2 ) and output resistance (957)(R diff_H2 ) can be determined by. For example, the gain is R diff_H2 / R diff_L2 It can be calculated as follows. The PWM controller (500) can determine whether OCP operation is performed using the current information amplified according to the gain sensed by the pin (503).

[0143] According to one embodiment, within the start-up period of the PWM controller (500), the gain may be changed. For example, within the start-up period, as the voltage applied to the pin (501) increases, the state of the gate of the transistor (961) of the second protection circuit (960) may be changed from OFF to ON. For example, the transistor (961) of the second protection circuit (960) may operate ON within the start-up period as the state of the first transistor (811) is changed. While the transistor (961) is driven ON, the resistance seen at the input terminal (955a) of the operational amplifier (955) may be defined as the parallel resistance between the input resistor (956) and the protection resistor (962). Accordingly, the gain may be changed within the start-up period. For example, the gain may be increased within the start-up period as the denominator value of the formula for calculating the gain is reduced by the parallel resistance. Accordingly, the PWM controller (500) may recognize a relatively low input current as a higher value (or current) according to the gain within the start-up period. Accordingly, the PWM controller (500) may perform the OCP operation (or function) even when a relatively low input current is used within the start-up period.

[0144] As described above, when an element of the power circuit (310) including the DC-DC converter is damaged, an overcurrent may occur in the power circuit (310). To protect against this, a protection circuit providing an OCP operation (function) may be used. Damage to the element may occur when stress accumulates in the elements of the power circuit (310). Therefore, to reduce the stress, the frequency of occurrence of the stress (e.g., the cycle of automatic recovery) may be reduced, or the level of the stress may be reduced. For example, the second protection circuit (950) of FIG. 9b may reduce the stress by relatively adjusting the OCP level.

[0145] In FIG. 9B, a control circuit (950) is illustrated in which the operational amplifier (955) is positioned externally to the PWM controller (500), but the present disclosure is not limited thereto. For example, the PWM controller (500) may include the operational amplifier (955). In this case, the second protection circuit (960) may be included within the PWM controller (500) as it is connected to the operational amplifier (955).

[0146] Figure 10 shows an example of a control circuit connected to a DC-DC converter.

[0147] The control circuit (1000) of FIG. 10 may be an example of the control circuit (320) of FIG. 3. For example, the control circuit (1000) may be connected to the power circuit (310) of FIG. 3. For example, the power circuit (310) may include a DC-DC converter, which is a resonant bus converter. For example, the control circuit (1000) may be connected to a gate of a transistor of the DC-DC converter. For example, the control circuit (1000) may generate a signal and control the operation of the transistor (or the gate) through the generated signal. For example, the signal may be referred to as a PWM signal.

[0148] According to one embodiment, the control circuit (1000) may include a PWM controller (500), a switching circuit (610), a voltage distribution circuit (710), a discharge circuit (810), a first protection circuit (910), an operational amplifier (955), and a second protection circuit (920). For example, the control circuit (1000) may include the PWM controller (500) of FIG. 5A. For example, the PWM controller (500) of the control circuit (1000) may include at least some of the plurality of pins included in the controller (500) of FIG. 5A. For example, the control circuit (1000) may include the switching circuit (610) of FIG. 6. For example, the switching circuit (610) may be connected to pin (504) of the PWM controller (500) and the discharge circuit (810). For example, the control circuit (1000) may include the voltage distribution circuit (710) of FIG. 7. For example, the voltage distribution circuit (710) may be connected to the pin (503) of the PWM controller (500). For example, the control circuit (1000) may include the discharge circuit (810) of FIG. 8. For example, the discharge circuit (810) may be connected to the pin (501) and the switching circuit (610) of the PWM controller (500). For example, the control circuit (1000) may include the first protection circuit (910). For example, the first protection circuit (910) may be connected to the pin (501) of the PWM controller (500). For example, the control circuit (1000) may include the second protection circuit (960). For example, the second protection circuit (960) can be connected to the operational amplifier (955) and the discharge circuit (810).

[0149] In FIG. 10, the control circuit (1000) is illustrated as including a switching circuit (610), a voltage distribution circuit (710), a discharge circuit (810), a first protection circuit (910), and a second protection circuit (960), but the present disclosure is not limited thereto. For example, the control circuit (1000) may include a switching circuit (610). For example, the control circuit (1000) may include a switching circuit (610) and a discharge circuit (810). For example, the control circuit (1000) may include a first protection circuit (910). For example, the control circuit (1000) may include a switching circuit (610), a discharge circuit (810), and a second protection circuit (960). The above-described examples are merely illustrative for convenience of description, and the present disclosure is not limited thereto. In other words, the control circuit (1000) may include a switching circuit (610), a voltage distribution circuit (710), a discharge circuit (810), a first protection circuit (910), a second protection circuit (960), or a combination of circuits.

[0150] Figures 11a and 11b illustrate examples of DC-DC converters including a damping circuit.

[0151] The DC-DC converter (1100) of FIG. 11A may be included in the power circuit (310) of FIG. 3. For example, the DC-DC converter (1100) may be connected to a control circuit (320). For example, the control circuit (320) may include the control circuit (600) of FIG. 6, the control circuit (700) of FIG. 7, the control circuit (800) of FIG. 8, the control circuit (900) of FIG. 9A, the control circuit (950) of FIG. 9B, or the control circuit (1000) of FIG. 10. For example, the control circuit (320) may generate a signal and control the operation of a transistor (or gate) of the DC-DC converter (1100) through the generated signal. For example, the signal may be referred to as a PWM signal.

[0152] According to one embodiment, the DC-DC converter (1100) may include a primary circuit (460). For example, the primary circuit (460) may output the input voltage of the power source to the output terminal (C Bus ) may include a transformer for converting the input voltage into an output voltage applied to the first portion (461) and the second portion (462). For example, the transformer may include a first portion (461) and a second portion (462). For example, the first portion (461) may be referred to as an input portion or input part. For example, the second portion (462) may be referred to as an output portion or output part. For example, the turns ratio (N) between the first portion (461) and the second portion (462) P : N S ), the output voltage converted from the input voltage (455) can be determined.

[0153] According to one embodiment, the DC-DC converter (1100) may include a plurality of transistors (1101, 1102, 1103, 1104). In the example of FIG. 11A, the DC-DC converter (1100) may include four transistors (1101, 1102, 1103, 1104) within the first portion (461) (or the input portion).

[0154] According to one embodiment, the gates of each of the transistors (1101, 1102, 1103, 1104) of the DC-DC converter (1100) may be connected to a control circuit (320). For example, the control circuit (320) may include a plurality of output pins (506, 507). For example, a first output pin (506) may be connected to a first transistor (1101) (Q1) and a fourth transistor (1104) (Q4). The first transistor (1101) (Q1) and the fourth transistor (1104) (Q4) may be referred to as a first set of transistors. For example, a second output pin (507) may be connected to a second transistor (1102) (Q2) and a third transistor (1103) (Q3). The second transistor (1102) (Q2) and the third transistor (1103) (Q3) may be referred to as a second set of transistors.

[0155] According to one embodiment, a PWM signal output from the control circuit (320) may be input to the gate. The PWM signal may be used to control the time for which the gate is driven. For example, when the operating frequency of the PWM signal is changed, the length of the time may be adjusted. The time may represent a period for which the gate operates ON. Referring to FIG. 11A, the PWM signals output from the control circuit (320) may selectively drive one of the first set of transistors and the second set of transistors. For example, when a PWM signal is output from the first output pin (506), the first set of transistors among the first set of transistors and the second set of transistors may be switched from OFF to ON. For example, when a PWM signal is output from the second output pin (507), the second set of transistors among the first set of transistors and the second set of transistors may be switched from OFF to ON. For example, the control circuit (320) may not output a PWM signal through the second output pin (507) while outputting a PWM signal through the first output pin (506). For example, the control circuit (320) may output a PWM signal through the second output pin (507) while not outputting a PWM signal through the first output pin (506).

[0156] According to one embodiment, the DC-DC converter (1100) includes an inductor (1110) (L) that performs a voltage converting operation through resonance. R ) and capacitor (C R ) may be included. For example, an inductor (1110) (L R ) is connected in series with the transformer and may be referred to as a series inductor. For example, the capacitor (C R) is connected in series with the transformer and may be referred to as a series capacitor. Inductor (1110) (L R ) and capacitor (C R ) may be referred to as an LLC converter.

[0157] According to one embodiment, the DC-DC converter (1100) may include a damping circuit (1120). For example, the damping circuit (1120) may include an inductor (1110) (L R ) may be arranged in parallel. For example, the damping circuit (1120) may include a damping capacitor (1121) and a damping resistor (1122). However, the present disclosure is not limited thereto. For example, the damping circuit (1120) may include a damping capacitor (1121).

[0158] According to one embodiment, the damping circuit (1120) can be used to prevent an increase in the output voltage of the DC-DC converter (1100) in a no load or light load situation. For example, the parasitic capacitors of the transistors (Q5, Q6, Q7, Q8) in the second part (462) can be used to prevent an increase in the output voltage of the DC-DC converter (1100) in a no load or light load situation. R ) operates as if connected in parallel with the inductor (1110) (L), the output voltage may increase without regulation. R ) can eliminate the influence of parasitic capacitors. Therefore, regulation of the output voltage can be performed in a no load or light load situation.

[0159] The DC-DC converter (1150) of FIG. 11B may be included in the power circuit (310) of FIG. 3. For example, the DC-DC converter (1150) may be connected to a control circuit (320). For example, the control circuit (320) may include the control circuit (600) of FIG. 6, the control circuit (700) of FIG. 7, the control circuit (800) of FIG. 8, the control circuit (900) of FIG. 9A, the control circuit (950) of FIG. 9B, or the control circuit (1000) of FIG. 10. For example, the control circuit (320) may generate a signal and control the operation of a transistor (or gate) of the DC-DC converter (1150) through the generated signal. For example, the signal may be referred to as a PWM signal.

[0160] According to one embodiment, the DC-DC converter (1150) may include a primary circuit (460). For example, the primary circuit (460) may output the input voltage of the power source to the output terminal (C O ) may include a transformer for converting the voltage applied to the output voltage. For example, the transformer may include a first portion (461) and a second portion (462). For example, the first portion (461) may be referred to as an input portion or input part. For example, the second portion (462) may be referred to as an output portion or output part. For example, the transformer may include a first capacitor (1162) (C r1 ) and the second capacitor (1172) (C r2 ) may be included. For example, the DC-DC converter (1150) may include a first capacitor (1162) (C r1 ) and the first inductor (1161) (L) arranged in series r1 ) may be included. For example, the DC-DC converter (1150) may include a second capacitor (1172) (C r2 ) and a second inductor (1171) (L) arranged in series r2) may be included. The first inductor (1161) (L r1 ) may be referred to as the first series inductor. The second inductor (1171) (L r2 ) may be referred to as a second series inductor.

[0161] According to one embodiment, the DC-DC converter (1150) may include a plurality of transistors (1151, 1152, 1153, 1154). In the example of FIG. 11A, the DC-DC converter (1150) may include four transistors (1101, 1102, 1103, 1104) within the first portion (461) (or the input portion).

[0162] According to one embodiment, the gates of each of the transistors (1151, 1152, 1153, 1154) of the DC-DC converter (1150) may be connected to a control circuit (320). For example, the control circuit (320) may include a plurality of output pins (506, 507). For example, a first output pin (506) may be connected to a first transistor (1151) (Q1) and a fourth transistor (1154) (Q4). The first transistor (1151) (Q1) and the fourth transistor (1154) (Q4) may be referred to as a first set of transistors. For example, a second output pin (507) may be connected to a second transistor (1152) (Q2) and a third transistor (1153) (Q3). The second transistor (1152) (Q2) and the third transistor (1153) (Q3) may be referred to as a second set of transistors.

[0163] According to one embodiment, a PWM signal output from the control circuit (320) may be input to the gate. The PWM signal may be used to control the time for which the gate is driven. For example, when the operating frequency of the PWM signal is changed, the length of the time may be adjusted. The time may represent a period for which the gate operates ON. Referring to FIG. 11B, the PWM signals output from the control circuit (320) may selectively drive one of the first set of transistors and the second set of transistors. For example, when a PWM signal is output from the first output pin (506), the first set of transistors among the first set of transistors and the second set of transistors may be switched from OFF to ON. For example, when a PWM signal is output from the second output pin (507), the second set of transistors among the first set of transistors and the second set of transistors may be switched from OFF to ON. For example, the control circuit (320) may not output a PWM signal through the second output pin (507) while outputting a PWM signal through the first output pin (506). For example, the control circuit (320) may output a PWM signal through the second output pin (507) while not outputting a PWM signal through the first output pin (506).

[0164] According to one embodiment, the DC-DC converter (1150) may include a plurality of damping circuits. For example, the DC-DC converter (1150) may include a first damping circuit (1180) and a second damping circuit (1190). For example, the first damping circuit (1180) may include a first inductor (1161) (L r1) may be arranged in parallel. For example, the first damping circuit (1180) may include a damping capacitor (1181) and a damping resistor (1182). However, the present disclosure is not limited thereto. For example, the first damping circuit (1180) may include a damping capacitor (1181). For example, the second damping circuit (1190) may include a second inductor (1171) (L r2 ) may be arranged in parallel. For example, the second damping circuit (1190) may include a damping capacitor (1191) and a damping resistor (1192). However, the present disclosure is not limited thereto. For example, the second damping circuit (1189) may include a damping capacitor (1191).

[0165] According to one embodiment, the first damping circuit (1180) and the second damping circuit (1190) can be used to prevent an increase in the output voltage of the DC-DC converter (1150) in a no load or light load situation. For example, parasitic capacitors of transistors (Q5, Q6, Q7, Q8) in the second portion (462) can be used to prevent the first inductor (1161) (L r1 ) and the second inductor (1171) (L r2 ) operates as if connected in parallel with the first inductor (1161) (L), the output voltage may increase without being regulated. r1 ) is arranged in parallel to the first damping circuit (1180) (or the second inductor (1171) (L r2 ) can eliminate the influence of parasitic capacitors. Therefore, regulation of the output voltage can be performed in a no load or light load situation.

[0166] The control circuit according to the present disclosure and the electronic device including the same may utilize a PWM controller (e.g., PWM controller (500)) and an additional circuit connected to the PWM controller (e.g., switching circuit (610) of FIG. 6, voltage distribution circuit (710) of FIG. 7, discharge circuit (810) of FIG. 8, first protection circuit (910) of FIG. 9A, second protection circuit (960) of FIG. 9B) or an additional circuit in a DC-DC converter connected to the PWM controller (e.g., damping circuit (1120) of FIG. 11A, first damping circuit (1180) and second damping circuit (1190) of FIG. 11B). The control circuit according to the present disclosure and the electronic device including the same may utilize a PWM controller (e.g., PWM controller (500)) in which PFM control is implemented so as to perform modulation of an operating frequency within the start-up period by adding an additional circuit to the control circuit or the electronic device (300). In addition, the control circuit according to the present disclosure and the electronic device including the same can reduce stress on components within a DC-DC converter using a PWM controller by adding an additional circuit to the control circuit or electronic device (300). Accordingly, the control circuit according to the present disclosure and the electronic device including the same can reduce production costs and reduce the size of the electronic device by using the additional circuit having a relatively simple configuration.

[0167] The effects that can be obtained from the present disclosure are not limited to the effects mentioned above, and other effects that are not mentioned can be clearly understood by a person having ordinary skill in the art to which the present disclosure belongs from the description below.

[0168] A control circuit for a DC (direct current)-DC converter as described above may include a PWM controller for generating a PWM signal applied to a gate of a transistor in the DC-DC converter. The control circuit may include a lumped element connected to a control pin of the PWM controller for adjusting an operating frequency (switching frequency) of the PWM signal that controls a time for which the gate is driven. The control circuit may include a first resistor to which a driving voltage of the PWM controller is applied. The control circuit may include a diode connected to the first resistor. The control circuit may include a capacitor arranged in parallel between the diode and the control pin, and a second resistor for discharging the capacitor.

[0169] According to one embodiment, the operating frequency of the PWM signal may be reduced as the capacitor is charged by the driving voltage within a start-up period of the PWM controller according to the first resistor and the capacitor. The operating frequency of the PWM signal may be adjusted according to the lumped element within a steady state period after the start-up period. Within the start-up period, the time for which the gate is driven may be increased as the operating frequency decreases. The length of the start-up period may be determined based on a resistance value of the first resistor and a capacitance of the capacitor.

[0170] In one embodiment, the first resistor may be connected to the anode of the diode. Each of the second resistor and the capacitor may be connected to the cathode of the diode. The lumped element may include at least one of a resistor and a capacitor.

[0171] In one embodiment, the control circuit may further include a discharge circuit. The discharge circuit may include a first transistor including a drain to which the driving voltage is applied. The discharge circuit may include a second transistor including a gate to which the driving voltage is applied and which is connected to the drain of the first transistor. The discharge circuit may include a resistor connecting between the drain of the second transistor and the capacitor.

[0172] According to one embodiment, the discharge circuit may be used to discharge the capacitor charged by the driving voltage during the start-up period in a fault state of the PWM controller. The PWM controller may further include a control pin for a duty of the PWM signal within the start-up period. The gate of the first transistor of the discharge circuit may be connected to the control pin.

[0173] In one embodiment, the control circuit may further include a first protection circuit. The first protection circuit may include a diode connected to the control pin. The first protection circuit may include a transistor having a drain to which the driving voltage is applied and a gate connected to the control pin. The first protection circuit may include a capacitor connected to the diode of the first protection circuit and a source of the transistor of the first protection circuit. The first protection circuit may be used to provide energy to the control pin through discharge of the capacitor of the first protection circuit charged during the start-up period while the voltage applied to the control pin of the PWM controller is reduced.

[0174] In one embodiment, the PWM controller may further include a current sensing pin for over current protection (OCP). The control circuit may further include a second protection circuit. The second protection circuit may include a protection resistor arranged in parallel with an input resistor connected to an input terminal of an amplifier, the input terminal including an output terminal connected to the current sensing pin. The second protection circuit may include a protection transistor having a drain connected to the protection resistor and a gate connected to the drain of the first transistor of the discharge circuit and the gate of the second transistor of the discharge circuit. The second protection circuit may be used to increase an output resistance between the input terminal and the output terminal of the amplifier and a gain of the amplifier based on the input resistance within the start-up period.

[0175] According to one embodiment, the control circuit may further include a duty resistor connected to the control pin and a duty capacitor connected to the duty resistor.

[0176] In one embodiment, the PWM controller may further include a current sensing pin for over current protection (OCP). The control circuit may further include a voltage division circuit. The voltage division circuit may include a first division resistor to which an input voltage of the DC-DC converter is applied. The voltage division circuit may include a second division resistor connected to the first division resistor and ground. The voltage division circuit may include a third division resistor connected to the first division resistor, the second division resistor, and the current sensing pin. The voltage division circuit may be used to adjust a threshold voltage for the OCP of the PWM controller using the input voltage of the DC-DC converter.

[0177] According to one embodiment, the DC-DC converter may include an LLC converter. The LLC converter may include a transformer. The LLC converter may include an inductor arranged in series with the transformer. The LLC converter may include a damping circuit arranged in parallel with the inductor. The damping circuit may include a resistor and a capacitor.

[0178] In one embodiment, the DC-DC converter may include a cap-isolation converter. The cap-isolation converter may include a first transformer circuit including a first inductor and a first capacitor arranged in series with the first inductor. The cap-isolation converter may include a second transformer circuit including a second inductor and a second capacitor arranged in series with the second inductor. The cap-isolation converter may include a damping circuit arranged in parallel with each of the first inductor and the second inductor. The damping circuit may include a resistor and a capacitor.

[0179] In one embodiment, the DC-DC converter may include a first set of transistors and a second set of transistors. The PWM controller may be connected to a gate of each of the transistors in the first set and a gate of each of the transistors in the second set. The PWM signal output by the PWM controller may selectively switch one of the first set and the second set.

[0180] In one embodiment, the DC-DC converter may include a first stage for converting an input voltage of the DC-DC converter, the first stage including the first set of transistors and the second set of transistors. The DC-DC converter may include second stages for providing the input voltage converted from the first stage to radio frequency (RF) circuits. The DC-DC converter may include the second stages arranged in parallel with each other.

[0181] According to one embodiment, the PWM controller may include a plurality of output pins. The PWM controller may further include a pin for adjusting a dead-time between PWM signals output from the plurality of output pins.

[0182] As described above, an electronic device may include a DC (direct current)-DC converter. The electronic device may include an electronic component to which a voltage converted by the DC-DC converter is applied. The electronic device may include a PWM controller for generating a PWM signal to be applied to a gate of a transistor in the DC-DC converter. The electronic device may include a lumped element connected to a control pin of the PWM controller for adjusting an operating frequency (switching frequency) of the PWM signal that controls a time for which the gate is driven. The electronic device may include a first resistor to which a driving voltage of the PWM controller is applied. The electronic device may include a diode connected to the first resistor. The electronic device may include a capacitor arranged in parallel between the diode and the control pin, and a second resistor for discharging the capacitor.

[0183] In one embodiment, the electronic component may include a radio frequency (RF) component. The RF component may include at least one of a power amplifier and a radio frequency integrated circuit (RFIC).

[0184] According to one embodiment, the operating frequency of the PWM signal may be reduced as the capacitor is charged by the driving voltage within a start-up period of the PWM controller according to the first resistor and the capacitor. The operating frequency of the PWM signal may be adjusted according to the lumped element within a steady state period after the start-up period. Within the start-up period, the time for which the gate is driven may be increased as the operating frequency decreases. The length of the start-up period may be determined based on a resistance value of the first resistor and a capacitance of the capacitor.

[0185] In one embodiment, the first resistor may be connected to the anode of the diode. Each of the second resistor and the capacitor may be connected to the cathode of the diode. The lumped element may include at least one of a resistor and a capacitor.

[0186] According to one embodiment, the electronic device may further include a discharge circuit connected to the PWM controller. The discharge circuit may include a first transistor including a drain to which the driving voltage is applied. The discharge circuit may include a second transistor including a gate to which the driving voltage is applied and which is connected to the drain of the first transistor. The discharge circuit may include a resistor connecting between the drain of the second transistor and the capacitor.

[0187] According to one embodiment, the discharge circuit may be used to discharge the capacitor charged by the driving voltage during the start-up period in a fault state of the PWM controller. The PWM controller may further include a control pin for a duty of the PWM signal within the start-up period. The gate of the first transistor of the discharge circuit may be connected to the control pin.

[0188] The methods according to the embodiments described in the claims or specification of the present disclosure may be implemented in the form of hardware, software, or a combination of hardware and software.

[0189] When implemented in software, a computer-readable storage medium storing one or more programs (software modules) may be provided. The one or more programs stored in the computer-readable storage medium are configured to be executed by one or more processors in an electronic device. The one or more programs include instructions that cause the electronic device to execute methods according to embodiments described in the claims or specification of the present disclosure. The one or more programs may be provided as a computer program product. The computer program product may be traded between a seller and a buyer as a commodity. The computer program product may be distributed in the form of a machine-readable storage medium (e.g., compact disc read only memory (CD-ROM)), or may be distributed online (e.g., downloaded or uploaded) through an application store (e.g., Play Store) or directly between two user devices (e.g., smart phones). In the case of online distribution, at least a portion of the computer program product may be temporarily stored or temporarily created in a device-readable storage medium, such as the memory of a manufacturer's server, an application store's server, or an intermediary server.

[0190] These programs (software modules, software) may be stored in random access memory, non-volatile memory including flash memory, read only memory (ROM), electrically erasable programmable read only memory (EEPROM), magnetic disc storage devices, compact disc-ROM (CD-ROM), digital versatile discs (DVDs) or other forms of optical storage devices, magnetic cassettes, or may be stored in memories formed by a combination of some or all of these. In addition, each configuration memory may include multiple copies.

[0191] Additionally, the program may be stored on an attachable storage device that is accessible via a communication network, such as the Internet, an intranet, a local area network (LAN), a wide area network (WAN), a storage area network (SAN), or a combination thereof. Such a storage device may be connected to a device implementing an embodiment of the present disclosure via an external port. Additionally, a separate storage device on the communication network may be connected to a device implementing an embodiment of the present disclosure.

[0192] In the specific embodiments of the present disclosure described above, components included in the disclosure are expressed singularly or plurally, depending on the specific embodiment presented. However, the singular or plural expressions are selected to suit the presented situation for convenience of explanation, and the present disclosure is not limited to singular or plural components. Components expressed in plural may be composed of singular elements, or components expressed in singular may be composed of plural elements.

[0193] According to embodiments, one or more of the components or operations of the aforementioned components may be omitted, or one or more other components or operations may be added. Alternatively or additionally, a plurality of components (e.g., modules or programs) may be integrated into a single component. In such a case, the integrated component may perform one or more functions of each of the plurality of components identically or similarly to those performed by the corresponding component among the plurality of components prior to the integration. According to embodiments, the operations performed by a module, program, or other component may be executed sequentially, in parallel, iteratively, or heuristically, or one or more of the operations may be executed in a different order, omitted, or one or more other operations may be added.

[0194] Meanwhile, although the detailed description of the present disclosure has described specific embodiments, it is obvious that various modifications are possible within the scope of the present disclosure.

Claims

1. In a control circuit for a DC(direct current)-DC converter, A PWM controller for generating a PWM (pulse width modulation) signal applied to the gate of a transistor in the DC-DC converter; A lumped element connected to a control pin of the PWM controller for adjusting the switching frequency of the PWM signal that controls the time for which the gate is driven; A first resistor to which the driving voltage of the above PWM controller is applied; a diode connected to the first resistor; and A capacitor arranged in parallel between the diode and the adjustment pin, and a second resistor for discharging the capacitor, Control circuit.

2. In claim 1, The operating frequency of the above PWM signal is: During the start-up period of the PWM controller according to the first resistor and the capacitor, the driving voltage decreases as the capacitor is charged, and Within the steady state section after the above start-up section, it is adjusted according to the concentration element, Within the above start-up period, the time for which the gate is driven increases as the operating frequency decreases, and The length of the above start-up section is determined based on the resistance value of the first resistor and the capacitance of the capacitor. Control circuit.

3. In claim 1, The above first resistor is connected to the anode of the diode, Each of the second resistor and the capacitor is connected to the cathode of the diode, and The above-mentioned concentrated element comprises at least one of a resistor and a capacitor, Control circuit.

4. In claim 1, The above control circuit further includes a discharge circuit, The above discharge circuit: A first transistor including a drain to which the driving voltage is applied; A second transistor having a gate connected to the drain of the first transistor and to which the driving voltage is applied; and Including a resistor connecting between the drain of the second transistor and the capacitor, Control circuit 5. In claim 4, The above discharge circuit is used to discharge the capacitor charged by the driving voltage during the start-up period in a fault state of the PWM controller, The above PMW controller further includes a control pin for the duty of the PWM signal within the start-up period, and The gate of the first transistor of the above discharge circuit is connected to the control pin, Control circuit.

6. In claim 5, The above control circuit further includes a first protection circuit, The above first protection circuit: A diode connected to the above control pin; A transistor including a drain to which the driving voltage is applied and a gate connected to the control pin; and Including a capacitor connected to the diode of the first protection circuit and the source of the transistor of the first protection circuit, The first protection circuit is used to provide energy to the control pin through the discharge of the capacitor of the first protection circuit charged during the start-up period while the voltage applied to the control pin of the PWM controller is reduced. Control circuit.

7. In claim 5, The above PWM controller further includes a current sensing pin for over current protection (OCP), The above control circuit further comprises a second protection circuit, The above second protection circuit: A protection resistor arranged in parallel with an input resistor connected to an input terminal of an amplifier including an output terminal connected to the current sensing pin; and A protection transistor including a drain connected to the protection resistor, and a gate connected to the drain of the first transistor of the discharge circuit and the gate of the second transistor of the discharge circuit, The second protection circuit is used to increase the output resistance between the input terminal and the output terminal of the amplifier and the gain of the amplifier based on the input resistance within the start-up period. Control circuit.

8. In claim 5, The above control circuit, Further comprising a duty resistor connected to the above control pin and a duty capacitor connected to the above duty resistor, Control circuit.

9. In claim 1, The above PWM controller further includes a current sensing pin for over current protection (OCP); The above control circuit further includes a voltage distribution circuit, The above voltage distribution circuit: A first distribution resistor to which the input voltage of the DC-DC converter is applied; a first distribution resistor and a second distribution resistor connected to ground; and Including the first distribution resistor, the second distribution resistor, and the third distribution resistor connected to the current sensing pin, The above voltage distribution circuit is used to adjust the threshold voltage for the OCP of the PWM controller by using the input voltage of the DC-DC converter. Control circuit.

10. In claim 1, The above DC-DC converter includes an LLC converter, The above LLC converter: transformer; An inductor placed in series with the above transformer; and A damping circuit is included which is arranged in parallel with the above inductor. The above damping circuit comprises a resistor and a capacitor. Control circuit.

11. In claim 1, The above DC-DC converter includes a cap-isolation converter, The above cap-insulated converter: A first transformer circuit including a first inductor and a first capacitor arranged in series with the first inductor; A second transformer circuit including a second inductor and a second capacitor arranged in series with the second inductor; and A damping circuit is included which is arranged in parallel with each of the first inductor and the second inductor, The above damping circuit comprises a resistor and a capacitor. Control circuit.

12. In claim 1, The above DC-DC converter comprises a first set of transistors and a second set of transistors, The PWM controller is connected to the gate of each of the transistors of the first set and the gate of each of the transistors of the second set, and The PWM signal output by the PWM controller selectively switches one of the first set and the second set. Control circuit.

13. In claim 12, The above DC-DC converter: A first stage for converting an input voltage of the DC-DC converter including the first set of transistors and the second set of transistors; and comprising second stages for providing the input voltage converted from the first stage to RF (radio frequency) circuits, and The above second stages are arranged parallel to each other, Control circuit.

14. In claim 1, The above PWM controller: multiple output pins; and Further including a pin for adjusting the dead-time between PWM signals output from the plurality of output pins. Control circuit.

15. In electronic devices, DC(direct current)-DC converter; An electronic component to which a voltage converted by the DC-DC converter is applied; A PWM controller for generating a PWM (pulse width modulation) signal applied to the gate of a transistor in the DC-DC converter; A lumped element connected to a control pin of the PWM controller for adjusting the switching frequency of the PWM signal that controls the time for which the gate is driven; A first resistor to which the driving voltage of the above PWM controller is applied; a diode connected to the first resistor; and A capacitor arranged in parallel between the diode and the adjustment pin, and a second resistor for discharging the capacitor, Electronic devices.

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