Antenna, communication method and terminal equipment

Abstract

The invention relates to the technical field of antennas, and provides an antenna, a communication method and terminal equipment, and the method comprises the steps: attaching a metal floor to a first surface of a dielectric substrate; the first excitation element and the second excitation element are respectively arranged on the first side and the second side of the metal floor, and the sizes of the two elements are related to a target frequency band; an inner conductor and an outer conductor of the first feed assembly are correspondingly connected with a first feed point of the first excitation element and the metal floor respectively; an inner conductor and an outer conductor of the second feed assembly are correspondingly connected with a second feed point of the second excitation element and the metal floor respectively; the first feed assembly is used for providing first excitation current for the first excitation element; the second feed assembly is used for providing a second excitation current for the second excitation element; the first excitation current and the second excitation current with different phase differences can present different current distributions on the metal floor, so that the purpose of antenna radiation beam steering is achieved, the technical effect of wide beams is achieved, and thus space direction coverage on a target frequency band is achieved.

Description

Technical Field

[0001] This application relates to the field of antenna technology, specifically to an antenna, a communication method, and a terminal device. Background Technology

[0002] Current terminal devices support satellite communication. Typically, a terminal device (e.g., a mobile phone) connects to a satellite to establish communication and fulfill communication needs. Satellites are generally classified according to their orbital altitude into geostationary orbit (GEO), medium Earth orbit (MEO), and low Earth orbit (LEO). The higher the orbit, the larger the ground area that the satellite can cover.

[0003] In related technologies, satellite communication refers to a direct connection between a terminal device and a high-orbit satellite (GEO or MEO) via a high-gain antenna. Because high-orbit satellites require a high signal strength from the terminal device's antenna, the user must align the antenna with the satellite and maintain a stable orientation to establish a connection. This satellite communication method is prone to high antenna power consumption, poor beam directionality, and instability.

[0004] Compared to high-Earth orbit (HEO) satellites, low-Earth orbit (LEO) satellite communication requires less antenna gain from terminal equipment. Antennas can establish communication with LEO satellites as long as they provide full space coverage, and users do not need to align their antennas with the LEO satellites to obtain more stable communication. However, antennas used in HEO satellite communication have high gain and directional beams, making them unsuitable for LEO satellite communication.

[0005] Therefore, there is an urgent need to provide a low-gain antenna with full space coverage to enable terminal devices to establish satellite communication with low-Earth orbit satellites. This would reduce the posture requirements for users to use terminal devices for satellite communication and improve the efficiency and stability of satellite communication. Summary of the Invention

[0006] This application provides an antenna, a communication method, and a terminal device that can improve the efficiency and stability of satellite communication.

[0007] In a first aspect, an antenna is provided for communication with a low-Earth orbit satellite system. The antenna includes: a dielectric substrate, a metal ground plane, a first excitation element, a second excitation element, a first feed assembly, and a second feed assembly. The metal ground plane is attached to a first surface of the dielectric substrate. The first excitation element is disposed on a first side of the metal ground plane, and the second excitation element is disposed on a second side of the metal ground plane. The dimensions of the first and second excitation elements are related to a target frequency band. The inner conductor of the first feed assembly is connected to a first feed point of the first excitation element, and the outer conductor of the first feed assembly is connected to the metal ground plane. The inner conductor of the second feed assembly is connected to a second feed point of the second excitation element, and the outer conductor of the second feed assembly is connected to the metal ground plane. The first feed assembly provides a first excitation current to the first excitation element. The second feed assembly provides a second excitation current to the second excitation element. The metal ground plane is used to achieve spatial directional coverage in the target frequency band by radiating beam steering under the action of the first and second excitation currents with different phase differences.

[0008] In this embodiment, the first excitation element and the second excitation element are respectively disposed on two sides (the first side and the second side) of the metal ground plane, so that the spatial distance between the two excitation elements (including the first excitation element and the second excitation element) is maximized, so as to excite different current modes on the metal ground plane. The inner conductor of the first feeding component is connected to the first feeding point of the first excitation element, and the outer conductor of the first feeding component is connected to the metal ground plane, forming a first feeding port. The inner conductor of the second feeding component is connected to the second feeding point of the second excitation element, and the outer conductor of the second feeding component is connected to the metal ground plane, forming a second feeding port. The first excitation element and the second excitation element share the same metal ground plane. After feeding the first feeding component and the second feeding component, that is, providing a first excitation current to the first feeding port and a second excitation current to the second feeding port, the first excitation current and the second excitation current can have different phase differences. With different phase differences, different current distributions can be presented on the metal ground plane, achieving the purpose of antenna radiation beam steering (i.e., the radiation angle changes), realizing the technical effect of wide beam, thereby achieving spatial directional coverage in the target frequency band.

[0009] The dimensions of the first and second excitation elements are inversely correlated with the target frequency band. The larger the center frequency of the target frequency band, the shorter the length of the excitation element (the first or second excitation element).

[0010] The first and second power supply components can be coaxial cables. A coaxial cable includes an outer conductor (or outer core) and an inner conductor (or inner core). The connection between the outer conductor and the metal ground plane, and the connection between the inner conductor and the excitation element, can be achieved by soldering. The power supply components provide current to the excitation element; under the influence of currents with different phase differences from the two excitation elements, different current distributions are excited on the metal ground plane.

[0011] The dielectric substrate can also be understood as a printed circuit board (PCB), and its material can be glass fiber, polyimide, polytetrafluoroethylene, etc., which is not limited in this application embodiment. The dielectric substrate includes a first surface and a second surface. A metal layer is plated on the entire surface of the first surface as a metal ground, that is, the length and width of the metal ground are the same as the length and width of the dielectric substrate; of course, a metal layer can also be plated on a large part of the middle area of ​​the first surface as a metal ground, which is not limited in this application embodiment. As long as the scheme of using two excitation elements to excite current on the same metal ground is within the protection scope of this application embodiment. The second surface is an insulating surface.

[0012] The metal floor has four sides. By placing two excitation elements on two different sides, the spatial distance between the two excitation elements can be maximized so that different current modes can be excited on the metal floor.

[0013] The target frequency band can be the frequency band in which the terminal equipment communicates with low-Earth orbit satellites. For example, the center frequency of the target frequency band can be 1.5 GHz.

[0014] The antenna for low-Earth orbit (LEO) satellite communication provided in this application achieves spatial coverage by adjusting the phase difference between the dual-feed ports to switch the current mode of the metal ground plane. The antenna is a wide-beam antenna, which significantly reduces the location requirements for user satellite communication. Users do not need to align themselves with the LEO satellite and maintain a stable posture to establish satellite communication, thus improving efficiency. Furthermore, because the wide-beam antenna has comprehensive coverage, even if the LEO satellite moves, the communication quality between the LEO satellite and the antenna will not be significantly affected, improving the stability of satellite communication.

[0015] In some possible implementations, the first current distribution and the second current distribution on the metal floor are orthogonal to each other, such that the radiation null point of the antenna under common-mode excitation is complementary to the radiation null point under differential-mode excitation. Here, the first current distribution refers to the current distribution on the metal floor when the first excitation current and the second excitation current are common-mode, and the second current distribution refers to the currents on the metal floor being orthogonal when the first excitation current and the second excitation current are differential-mode.

[0016] The first feeding component feeds the first feeding port, exciting a current on the metal ground through the first excitation element; the second feeding component feeds the second feeding port, exciting a current on the metal ground through the second excitation element. When the first and second excitation currents are common-mode, i.e., the phase difference between the excitation currents of the first and second feeding components is 0°, a first current distribution is excited on the metal ground. When the first and second excitation currents are differential-mode, the phase difference between the feeding currents of the first and second feeding components is 180°, and a second current distribution is excited on the metal ground.

[0017] The first and second current distributions are orthogonal to each other, and the antenna's radiation beam under common-mode excitation is orthogonal to the antenna's radiation beam under differential-mode excitation. That is, areas with weaker radiation under common-mode excitation are precisely areas with stronger radiation under differential-mode excitation, and vice versa. Furthermore, the radiation null points under common-mode excitation and differential-mode excitation are complementary. The antenna achieves full-space beam coverage under different phase differences, thus achieving a wide beam and high coverage, suitable for low-Earth orbit (LEO) satellite communication. LEO communication can be established without requiring the user to align with the LEO satellite and maintain a stable attitude, improving the efficiency and stability of satellite communication.

[0018] In some possible implementations, the structures of the first and second excitation elements are axially or centrally symmetric on the metal floor.

[0019] In this embodiment, axisymmetry can also be called mirror symmetry. The first excitation element and the second excitation element are symmetrical along the axis of the metal ground plane, or the first excitation element and the second excitation element are centrally symmetrical along the center point of the metal ground plane. This increases the diversity and richness of the antenna structure.

[0020] By setting two excitation elements (including the first excitation element and the second excitation element) that are either axisymmetric or centrosymmetric, the symmetry of the antenna radiation beam can be improved, thereby increasing the coverage of the antenna beam.

[0021] In some possible implementations, the metal floor is a rectangular structure; the first and second sides are either the two long sides of the metal floor or the two short sides of the metal floor.

[0022] If two excitation elements (including the first excitation element and the second excitation element) are close together, it will cause beam orientation, thereby reducing coverage. Therefore, in this embodiment, the two excitation elements are set on two parallel sides, which can be set on the two short sides or the two long sides, and this embodiment does not limit the setting.

[0023] For example, the antenna is used in a terminal device, which includes a top edge, a bottom edge, and two sides. Similarly, the metal ground plane also has a top edge, a bottom edge, and two sides. The first and second edges can be the two sides of the metal ground plane, or the first and second edges can be the top and bottom edges of the metal ground plane, so that the positions of the two excitation elements need to be staggered as much as possible to improve the coverage of the antenna beam.

[0024] Antennas are ultimately used in terminal devices with different structures. These devices usually contain other components. By increasing the diversity of antenna structures, different forms can be adopted according to specific needs, thus increasing the probability of antenna implementation.

[0025] In some possible implementations, the outer conductor of the first power supply component is connected to a first region of the metal ground plane; the vertical distance between the first region and the first power supply point is less than a first distance threshold; the outer conductor of the second power supply component is connected to a second region of the metal ground plane; the vertical distance between the second region and the second power supply point is less than a second distance threshold.

[0026] In this embodiment, the outer conductors of both the first feed assembly and the second feed line assembly are connected to a metal ground plane, meaning the two excitation elements share the same metal ground plane. Taking welding as an example, the outer conductor can be directly welded to the metal ground plane. This method eliminates the need for metal on the second surface of the dielectric substrate and for through-holes inside the substrate, simplifying antenna design. Alternatively, a metal plate connected to a through-hole in the metal ground plane can be provided on the second surface of the dielectric substrate, and the outer conductor can be welded to this plate, thus connecting the outer conductor to the metal ground plane. In this method, the connection points of the outer and inner conductors of the feed assembly are both on the second surface of the dielectric substrate, without affecting the layout of the metal ground plane, increasing the feasibility of antenna implementation. Both connection methods can achieve the connection between the outer conductor and a specific area (i.e., the first area or the second area) on the metal ground plane.

[0027] Since this embodiment utilizes two excitation elements to generate current on the same metal floor, the welding positions of the outer and inner conductors of the feeding assembly (first feeding assembly or second feeding assembly) cannot be too far apart. Excessive distance may prevent proper current generation. The inner conductor of the feeding assembly is connected to the feed point of the excitation element, and the connection area of ​​the outer conductor of the feeding assembly on the metal floor cannot be too far from the feed point. Therefore, by setting the vertical distance between the first feed point and the first region to be less than a first distance threshold, the first region is brought closer to the first feed point; similarly, the vertical distance between the second feed point and the second region is set to be less than a second distance threshold, bringing the second region closer to the second feed point. Thus, by feeding two excitation elements with two feeding assemblies respectively, current can be generated on the metal floor, achieving full-space coverage under different phase differences and improving antenna beam coverage.

[0028] It should be noted that the first distance threshold and the second distance threshold can be appropriately set by those skilled in the art according to the actual situation. The first distance threshold and the second distance threshold can be equal or unequal. The first distance threshold and the second distance threshold are used to limit the relative position of the outer conductor and the inner conductor, so as to better excite current on the metal floor. The first distance threshold and the second distance threshold can be set to a smaller value, for example, slightly larger than the thickness of the dielectric substrate. This application embodiment does not limit this, as long as it can ensure that the two excitation elements excite current on the metal floor.

[0029] In some possible implementations, the first excitation element includes a first slot and a first matching plate, with a first feed point disposed on the first matching plate; the second excitation element includes a second slot and a second matching plate, with a second feed point disposed on the second matching plate; the first slot extends in a direction away from the first side; the first matching plate is disposed on the second surface of the dielectric substrate and close to the first side, for impedance matching of the first slot in the target frequency band; the projection of the first matching plate onto the metal floor and the first region are respectively located on both sides of the first slot; the second slot extends in a direction away from the second side; the second matching plate is disposed on the second surface and close to the second side, for impedance matching of the second slot in the target frequency band; the projection of the second matching plate onto the metal floor and the second region are respectively located on both sides of the second slot.

[0030] In this embodiment, the first gap is formed by slotting (or grooving) along the first side away from the metal floor. The length of the first gap is inversely correlated with the target frequency band; the higher the frequency of the target band, the shorter the length of the first gap. The length of the first gap is slightly greater than one-quarter of the wavelength of the center frequency of the target band on the dielectric substrate. To facilitate the excitation of current on the metal floor, the extension direction of the first gap is away from the first side. The first gap may include multiple segments. The starting segment of the first gap may be perpendicular to the first side, or the angle between the starting segment of the first gap and the first side may be greater than a preset angle, such as 45°, 60°, etc. This embodiment does not limit this, as long as the extension direction of the first gap is away from the first side.

[0031] The first slot is designed to generate current in the target frequency band, enabling the antenna to operate within that band. Therefore, impedance matching is required for the first slot. This necessitates the placement of a first matching piece on the second surface of the dielectric substrate. This first matching piece can be a small piece of metal attached to the second surface of the substrate. The first matching piece forms a capacitor with the metal ground plane. Adjusting the size of the first matching piece adjusts the antenna's impedance. The length of the first slot is related to the inductance in the antenna's impedance; adjusting the length of the first slot adjusts the antenna's impedance as well. The size of the first matching piece and the length of the first slot are used for impedance matching of the first slot in the target frequency band.

[0032] The first feed point can be the center point of the first matching piece or another location. The inner conductor of the first feed assembly is connected to the first feed point on the first matching piece, and the outer conductor of the first feed assembly is connected to a first region on the metal ground plane to provide excitation to the first slot. Therefore, the first matching piece and the first region should be located near the first slot and on both sides of the first slot. In the antenna of this embodiment, the first matching piece can be disposed on the second surface of the dielectric substrate and close to the first side, with the projection of the first matching piece on the metal ground plane and the first region located on both sides of the first slot, respectively.

[0033] The first slot and the first matching piece serve as impedance matching elements, acting as a parallel inductor and a series capacitor, respectively. The inductance can be adjusted by changing the length of the first slot, and the capacitance can be adjusted by changing the size of the first matching piece. This allows the antenna to achieve impedance matching at the target frequency band, thereby reducing losses during energy radiation after connection to the first feeding assembly.

[0034] Correspondingly, the second gap can be formed by slotting along the second side away from the metal floor. The length of the second gap is related to the target frequency band. To facilitate the excitation of current on the metal floor, the extension direction of the second gap is away from the second side. The second gap can include multiple segments. The starting segment of the second gap can be perpendicular to the second side, or the angle between the starting segment of the second gap and the second side can be greater than a preset angle, such as 45°, 60°, etc. This application embodiment does not limit this, as long as the extension direction of the second gap is away from the second side.

[0035] The second slot is used to excite current in the target frequency band, enabling the antenna to operate in that band. Therefore, impedance matching is required for the second slot. This involves placing a second matching piece on the second surface of the dielectric substrate. The second matching piece can be a small piece of metal attached to the second surface of the substrate. The second matching piece forms a capacitor with the metal ground plane. Adjusting the size of the second matching piece adjusts the antenna impedance. The length of the second slot is related to the inductance in the antenna impedance; adjusting the length of the second slot adjusts the antenna impedance. The size of the second matching piece and the length of the second slot are used for impedance matching of the second slot in the target frequency band.

[0036] The second feed point can be the center point of the second matching piece or other locations. The inner conductor of the second feed assembly is connected to the second feed point on the second matching piece, and the outer conductor of the second feed assembly is connected to a second region on the metal ground plane to provide excitation to the second slot. Therefore, the second matching piece and the second region should be located near the second slot and on both sides of the second slot. In the antenna of this embodiment, the second matching piece can be disposed on the second surface of the dielectric substrate and close to the second side, with the projection of the second matching piece on the metal ground plane and the second region located on both sides of the second slot, respectively.

[0037] The second slot and the second matching plate serve as impedance matching elements, acting as a parallel inductor and a series capacitor, respectively. The inductance can be adjusted by changing the length of the second slot, and the capacitance can be adjusted by changing the size of the second matching plate. This allows the antenna to achieve impedance matching at the target frequency band, thereby reducing energy loss during energy radiation after connection to the second feed assembly.

[0038] In this embodiment, the method of slotting the metal floor allows the two gaps (the first gap and the second gap) to directly excite the current on the metal floor. The manufacturing process is simple, requires no additional components, and reduces the complexity of the antenna while ensuring that the antenna can achieve a wide beam.

[0039] In some possible implementations, the first excitation element further includes a first grounding plate disposed on the second surface and close to the first side, the projection of the first grounding plate onto the metal floor overlapping the first region, and a through hole connecting the first grounding plate and the metal floor; the outer conductor of the first power supply component is connected to the first grounding plate; and / or, the second excitation element further includes a second grounding plate disposed on the second surface and close to the second side, the projection of the second grounding plate onto the metal floor overlapping the second region, and a through hole connecting the second grounding plate and the metal floor; the outer conductor of the second power supply component is connected to the second grounding plate.

[0040] In this embodiment, the first grounding plate is disposed on the first surface of the dielectric substrate and connected to the metal ground plane via a through hole. Thus, the connection between the outer conductor of the first power supply component and the first grounding plate enables connection to the metal ground plane. The first grounding plate can be made of a small piece of metal attached to the second surface of the dielectric substrate.

[0041] The second grounding plate is disposed on the first surface of the dielectric substrate and connected to the metal ground plane via a through-hole. Thus, the outer conductor of the second power supply component can be connected to the metal ground plane by connecting the second grounding plate. The second grounding plate can be made of a small piece of metal attached to the second surface of the dielectric substrate.

[0042] It should be noted that both the first grounding piece and the second grounding piece are used to connect to the external conductor. The size of the grounding piece (the first grounding piece or the second grounding piece) can be appropriately set by those skilled in the art according to the actual situation. For example, taking the connection by welding as an example, the grounding piece can be set to be slightly larger than the welding area. This application embodiment does not limit this, as long as it can be connected to the external conductor.

[0043] In the antenna, the first excitation element may include a first grounding piece connected to a through-hole in the metal ground plane, and a first feeding component connected to the first grounding piece; alternatively, the first excitation element may not include the first grounding piece, and the first feeding component is connected to a first region. Similarly, the second excitation element may include a second grounding piece connected to a through-hole in the metal ground plane, and a second feeding component is connected to the second grounding piece; alternatively, the second excitation element may not include the second grounding piece, and the second feeding component is connected to a second region. The excitation element in the antenna can be any combination of the above embodiments. For example, the first excitation element includes the first grounding piece, and the second excitation element does not include the first grounding piece; the first excitation element does not include the first grounding piece, and the second excitation element includes the first grounding piece; both the first and second excitation elements include grounding pieces; and neither the first nor the second excitation element includes a grounding piece. This application does not limit the specific possibilities in this regard.

[0044] In this embodiment, the connection points of the outer conductor and inner conductor of the feeding component are both on the second side of the dielectric substrate, which does not affect the layout of the metal ground plane and improves the possibility of antenna implementation.

[0045] In some possible implementations, the first or second gap can be any one of an L-shaped structure, a straight line structure, an arc structure, or a broken line structure.

[0046] The first and second slots are designed to induce different current distributions on the metal ground plane under the influence of excitation currents with different phase differences. Therefore, the structural designs of the first and second slots can be diverse, such as L-shaped, straight, arc-shaped, or polygonal structures, as long as they can induce current on the metal ground plane. This increases the diversity and richness of antenna structures.

[0047] In the antenna, the structures of the first slot and the second slot can be the same or different. The slots in the antenna can be any combination of the above structures. For example, the structures of the first slot and the second slot can both be L-shaped; the structure of the first slot can be L-shaped and the structure of the second slot can be arc-shaped, etc. The embodiments of this application do not limit this.

[0048] The antenna will ultimately be used in terminal devices with different structures. Other components are usually placed in the terminal devices. This example increases the diversity of antenna structures, allowing different forms to be adopted according to specific needs, thus increasing the probability of antenna implementation.

[0049] In some possible implementations, the starting end of the first slit is located at the center of the first side, and the starting end of the second slit is located at the center of the second side; or, the starting ends of the first slit and the starting ends of the second slit are centrally symmetrical.

[0050] In this embodiment, the starting end of the first slot is located at the center of the first side and extends in a direction away from the first side (or in a direction closer to the second side). Similarly, the starting end of the second slot is located at the center of the second side and extends in a direction away from the second side (or in a direction closer to the first side). Thus, by setting the starting segments of the two slots (the first slot and the second slot) at the center, and feeding through two feed ports (i.e., dual feed ports), the current distribution excited on the metal ground plane can improve the symmetry of the antenna radiation beam, thereby improving the antenna beam coverage.

[0051] In this embodiment, the starting end of the first slot is located on the first side, and the starting end of the second slot is located on the second side, with the two positions being centrally symmetrical about the center point of the metal ground plane. For example, the starting end of the first slot is located slightly above the first side, and the starting end of the second slot is located slightly below the first side. Thus, by setting centrally symmetrical starting ends, the current distribution excited on the metal ground plane after feeding through the two feed ports can improve the symmetry of the antenna radiation beam, thereby improving the antenna beam coverage.

[0052] In some possible implementations, the projection of the first matching piece onto the metal floor coincides with the first gap; and / or, the projection of the second matching piece onto the metal floor coincides with the second gap.

[0053] In this embodiment, the first matching piece is located on the second surface of the dielectric substrate. The first matching piece and the metal ground plane form a capacitor. The impedance of the antenna can be adjusted by adjusting the size of the first matching piece. The inner conductor of the first feeding assembly is connected to the first feeding point on the first matching piece to provide excitation to the first slot. The first matching piece should be located near the first slot. In this example, the first matching piece can be located slightly above the first slot, meaning that the projection of the first matching piece onto the metal ground plane overlaps with the first slot.

[0054] Similarly, in this example, the second matching piece can also be positioned slightly above the second gap, meaning that the projection of the second matching piece onto the metal floor overlaps with the second gap.

[0055] In some possible implementations, the areas of the first and second matching plates facing the metal ground plane, as well as the lengths of the first and second gaps, are related to the size and dielectric constant of the dielectric substrate at the target frequency band.

[0056] This application provides a design concept for a wide-beam antenna. Two slots are set on the same metal floor, and two feeding components are used to feed the two slots respectively. Current can be excited on the metal floor, and full space coverage can be achieved under the action of different phase differences, thereby improving the coverage of the antenna beam.

[0057] For the target frequency band, different dielectric constants, thicknesses, or even different lengths and widths of dielectric substrates will result in different gap lengths and matching plate sizes. Based on the above design concept, impedance matching for the target frequency band can be achieved by adjusting the gap length and matching plate size. This reduces losses during energy radiation after connection to the power supply component.

[0058] Similarly, for different target frequency bands, impedance matching can be achieved by adjusting the length of the gap and the size of the matching plate, based on the above design concept. This reduces losses during energy radiation after connection to the power supply components.

[0059] Furthermore, the structure of each of the two gaps, their respective locations, and their relative positions all have a slight impact on impedance matching in the target frequency band. Here, impedance matching in the target frequency band can be achieved by fine-tuning the length of the gaps and the size of the matching piece.

[0060] The design concept of the wide-beam antenna provided in this application embodiment has no limitations on the target frequency band, dielectric constant, thickness, length and width of the substrate. By adjusting the length of the slot and the size of the matching plate, it is possible to excite a current on the metal ground after feeding the two slots separately, and achieve full space coverage under the action of different phase differences, thereby improving the coverage of the antenna beam.

[0061] In some possible implementations, a first groove corresponding to the structure and position of the first gap is formed on the dielectric substrate; and / or, a second groove corresponding to the structure and position of the second gap is formed on the dielectric substrate.

[0062] The above embodiment involves creating grooves in the metal substrate to form two gaps, without modifying the dielectric substrate. Unwanted metal on the metal substrate can be removed using photolithography to achieve the grooves. In this example, the dielectric substrate can also be grooved, i.e., etched through it. This removes the metal substrate attached to the first surface of the dielectric substrate. In other words, grooves corresponding to the structure and position of the gaps are also created on the dielectric substrate.

[0063] It should be noted that the length of the slot and the size of the matching plate described above, which are applicable to slotting only on a metal floor, cannot be directly applied to the scheme of slotting on a dielectric substrate. For the scheme of slotting on a dielectric substrate, it is necessary to use antenna simulation software to fine-tune the length of the slot and the size of the matching plate to achieve impedance matching in the target frequency band, and then process the dielectric substrate to obtain an antenna with slots on the dielectric substrate.

[0064] This application provides a technical solution for slotting on a dielectric substrate, which increases the diversity of antenna manufacturing processes and the diversity and richness of antenna structures.

[0065] In some possible implementations, the first excitation element is the first radial branch of the inverted F structure, and the second excitation element is the second radial branch of the inverted F structure; the first short-circuit point of the first radial branch is connected to the first connection point of the metal ground plane, and the first connection point is the point on the metal ground plane closest to the first short-circuit point; the second short-circuit point of the second radial branch is connected to the second connection point of the metal ground plane, and the second connection point is the point on the metal ground plane closest to the second short-circuit point.

[0066] This application provides a design concept for a wide-beam antenna. Two feeding components feed two feeding ports respectively, with both ports sharing the same metal ground plane. Current can be excited on the metal ground plane, and under the influence of different phase differences, full-space coverage can be achieved, improving the antenna beam coverage. Based on this, this application can also incorporate inverted-F radiating stubs. Two inverted-F radiating stubs can excite different current modes on the metal ground plane, achieving beam steering and reaching the technical effect of full-space coverage. This increases the diversity and richness of antenna structures.

[0067] Furthermore, the two inverted-F radiating stubs can be part of the metal frame of the terminal device. Optimizing the antenna design within the limited space of the terminal device, while minimizing changes to the existing structure, reduces the complexity of the antenna design and increases the feasibility of antenna implementation.

[0068] In some possible implementations, the first excitation element and the second excitation element are connected to form a third radiating branch.

[0069] The antenna provided in this application embodiment achieves low gain and full-space coverage by adjusting the phase difference between two feed ports. Essentially, this scheme uses two feed ports sharing a common metal ground plane as the radiator to realize a wide-beam antenna. Based on this, the two excitation elements (including a first excitation element and a second excitation element) provided in this application embodiment can be connected together to form the same radiating stub (i.e., a third radiating stub). The length of the third radiating stub is related to the target frequency band. The third radiating stub has two feed ports, meaning it includes two feed points (including a first feed point and a second feed point). The first feed point and the second feed point can be located on the same side of the metal ground plane (e.g., any side of the metal ground plane), i.e., the first side and the second side are the same side. Alternatively, the first feed point and the second feed point can be located on any two sides of the metal ground plane; these two sides can be parallel or adjacent. The third radiating stub is fed by two feeding components (including the first feeding component and the second feeding component), so that the metal ground can achieve spatial directional coverage in the target frequency band by radiating beam steering under the action of excitation current with different phase differences.

[0070] In this embodiment, a third radiating stub can be set up, and the current mode switching of the metal ground plane can be achieved by adjusting the phase difference between the dual-feed ports, which increases the diversity and richness of the antenna structure.

[0071] Secondly, a terminal device is provided, which includes any of the antennas described in the first aspect; the terminal device communicates with a low-orbit satellite system via the antenna.

[0072] In some possible implementations, the terminal device has a foldable structure; the metal ground plane in the antenna has a foldable structure; or, the terminal device includes two independent metal ground planes, and the metal ground plane in the antenna is either an independent metal ground plane.

[0073] Thirdly, a communication method is provided, which is applied to any of the terminal devices mentioned in the second aspect; the method includes: providing current to the first feeding component and the second feeding component of the antenna of the terminal device according to multiple preset phase differences, and obtaining the signal strength corresponding to each of the multiple preset phase differences when the terminal device communicates with a low-orbit satellite system; providing current to the first feeding component and the second feeding component of the antenna according to the phase difference corresponding to the maximum value among the multiple signal strengths, so as to maximize the radiation intensity of the antenna.

[0074] In this embodiment, without knowing the position of the low-Earth orbit satellite, multiple preset phase differences are traversed, and the signal strength corresponding to each preset phase difference during communication between the terminal device and the low-Earth orbit satellite system is obtained. The phase difference with the largest signal strength is selected. During communication, current is supplied to the two feed components of the antenna according to this phase difference, which maximizes the antenna's radiation intensity.

[0075] This communication method places no restrictions on the user's terminal device posture, reducing the location requirements for satellite communication and improving its efficiency. Furthermore, because wide-beam antennas offer comprehensive coverage, even if the low-Earth orbit (LEO) satellite moves, the communication quality between the LEO satellite and the antenna will not be significantly affected, thus improving the stability of satellite communication.

[0076] Fourthly, a communication method is provided, which is applied to any of the terminal devices described in the second aspect. The method includes: acquiring the positional relationship between a low-Earth orbit (LEO) satellite system and the terminal device, and the polarization mode of the LEO satellite system; determining a target phase difference based on the positional relationship, polarization mode, and a phase distribution map corresponding to the spatial radiation gain of the terminal device's antenna; the phase distribution map indicating the phase difference corresponding to the maximum gain at each spatial point under different polarization modes; and providing current to the first and second feeding components of the antenna according to the target phase difference, so that the radiation intensity of the antenna at the position facing the LEO satellite system is maximized.

[0077] In this embodiment, knowing the relative positions of the low-Earth orbit satellite and the terminal device, the target phase difference with the highest antenna gain can be directly selected from the phase distribution map with the same polarization as the low-Earth orbit satellite system, based on the positional relationship. During communication, current is supplied to the two feed components of the antenna according to this phase difference, maximizing the radiation intensity at the antenna's position towards the low-Earth orbit satellite system.

[0078] This communication method is applicable to situations where the positional relationship between a low-Earth orbit satellite system and a terminal device is relatively fixed. It can directly filter out suitable phase differences, thereby improving the efficiency of satellite communication. Attached Figure Description

[0079] Figure 1 This is a schematic diagram of the structure of a terminal device provided in an embodiment of this application;

[0080] Figure 2 This is a spherical spatial polarization distribution map provided in an embodiment of this application;

[0081] Figure 3 This is a schematic diagram of a conventional dipole two-element array provided in an embodiment of this application;

[0082] Figure 4 This is a schematic diagram of the radiation modes of a traditional dipole two-element array under different excitations, provided in an embodiment of this application.

[0083] Figure 5 This is a schematic diagram of antenna 1 provided in an embodiment of this application. Figure 1 ;

[0084] Figure 6 This is a schematic diagram of antenna 1 provided in an embodiment of this application. Figure 2 ;

[0085] Figure 7 These are schematic diagrams of different forms of antennas provided in the embodiments of this application. Figure 1 ;

[0086] Figure 8 These are schematic diagrams of different forms of antennas provided in the embodiments of this application. Figure 2 ;

[0087] Figure 9 These are schematic diagrams of different forms of antennas provided in the embodiments of this application. Figure 3 ;

[0088] Figure 10 These are schematic diagrams of different forms of antennas provided in the embodiments of this application. Figure 4 ;

[0089] Figure 11 This is a schematic diagram of the current distribution of antenna 1 provided in an embodiment of this application;

[0090] Figure 12 This is a schematic diagram of the radiation modes of antenna 1 under different excitations provided in the embodiments of this application;

[0091] Figure 13 This is a schematic diagram of the active return loss of the dual-feed port of antenna 1 provided in this application embodiment under eight phase differences;

[0092] Figure 14 This is a schematic diagram of the two-dimensional radiation modes of the dual-feed port of antenna 1 provided in this application, with right-hand circular gain under eight phase differences;

[0093] Figure 15 This is the combined gain radiation pattern of antenna 1 provided in the embodiments of this application;

[0094] Figure 16 This is a phase distribution diagram of antenna 1 provided in an embodiment of this application;

[0095] Figure 17 This is a spatial coverage curve of the right-hand rotation gain of antenna 1 provided in the embodiments of this application;

[0096] Figure 18 This is a schematic diagram of a satellite communication provided in an embodiment of this application;

[0097] Figure 19 This is a schematic diagram of the physical structure of antenna 1 provided in an embodiment of this application;

[0098] Figure 20 This is a schematic diagram of the actual test environment of antenna 1 provided in the embodiments of this application;

[0099] Figure 21 This is a comparison diagram of the actual test and simulation return loss of antenna 1 provided in the embodiments of this application;

[0100] Figure 22 This is a schematic diagram of the phase distribution of antenna 1 as actually tested in the embodiments of this application;

[0101] Figure 23 This is the combined gain radiation pattern of antenna 1 as actually tested in the embodiments of this application;

[0102] Figure 24 This is a comparison chart of the actual test and simulation coverage of antenna 1 provided in the embodiments of this application;

[0103] Figure 25 This is a schematic diagram of antenna 2 provided in an embodiment of this application;

[0104] Figure 26 This is a schematic diagram of the current distribution of antenna 2 provided in an embodiment of this application;

[0105] Figure 27 This is a schematic diagram of the radiation modes of antenna 2 under different excitations provided in the embodiments of this application;

[0106] Figure 28 This is a spatial coverage curve of the right-hand rotation gain of antenna 1 and antenna 2 provided in the embodiments of this application;

[0107] Figure 29This is a schematic diagram of the antenna 3 provided in the embodiments of this application. Figure 1 ;

[0108] Figure 30 This is a schematic diagram of the antenna 3 provided in the embodiments of this application. Figure 2 ;

[0109] Figure 31 This is a schematic diagram of the current distribution of antenna 3 provided in an embodiment of this application;

[0110] Figure 32 This is a schematic diagram of the radiation modes of antenna 3 under different excitations provided in the embodiments of this application;

[0111] Figure 33 This is a schematic diagram of antenna 4 provided in an embodiment of this application;

[0112] Figure 34 This is an exemplary flowchart of a communication method provided in an embodiment of this application;

[0113] Figure 35 This is an exemplary flowchart of another communication method provided in the embodiments of this application. Detailed Implementation

[0114] The technical solutions of the embodiments of this application will be described below with reference to the accompanying drawings. In the description of the embodiments of this application, unless otherwise stated, " / " means "or," for example, A / B can mean A or B; "and / or" in this text is merely a description of the relationship between related objects, indicating that three relationships can exist. For example, A and / or B can represent: A existing alone, A and B existing simultaneously, and B existing alone. Furthermore, in the description of the embodiments of this application, "multiple" refers to two or more than two.

[0115] Hereinafter, the terms "first," "second," and "third" are used for descriptive purposes only and should not be construed as indicating or implying relative importance or implicitly specifying the number of technical features indicated. Thus, a feature defined as "first," "second," or "third" may explicitly or implicitly include one or more of that feature.

[0116] The antenna provided in this application embodiment can be applied to terminal devices such as mobile phones, foldable mobile phones, tablet computers, wearable devices, vehicle-mounted devices, augmented reality (AR) / virtual reality (VR) devices, laptops, ultra-mobile personal computers (UMPCs), netbooks, and personal digital assistants (PDAs). This application embodiment does not impose any restrictions on the specific type of terminal device.

[0117] Please refer to Figure 1 This is a schematic diagram of the structure of a terminal device provided in an embodiment of this application. Figure 1 As shown, the terminal device 100 provided in this application embodiment can be arranged in the following order from top to bottom along the z-axis: screen and cover plate 101, metal shell 102, internal structure 103, and back cover 104.

[0118] The screen and cover plate 101 can be used to realize the display function of the terminal device 100. The metal casing 102 can serve as the main frame of the terminal device 100, providing rigid support for the terminal device 100. The internal structure 103 can include a collection of electronic and mechanical components that realize the various functions of the terminal device 100. For example, the internal structure 103 can include shielding covers, screws, reinforcing ribs, etc. The back cover 104 can be the rear exterior surface of the terminal device 100, and the back cover 104 can be made of glass, ceramic, plastic, etc. in different implementations.

[0119] The antenna provided in this application embodiment can be applied to, for example... Figure 1 The terminal device 100 shown herein is used to support the wireless communication function of the terminal device 100. In some embodiments, the antenna may be disposed on the metal housing 102 of the terminal device 100, and correspondingly, the dielectric substrate may be the metal housing 102, with a metal ground plane attached to the first surface (i.e., the bottom surface) of the dielectric substrate. In other embodiments, the antenna involved in this antenna scheme may be disposed on the rear cover 104 of the terminal device 100, and correspondingly, the dielectric substrate may be the rear cover 104, with a metal ground plane attached to the bottom surface of the dielectric substrate.

[0120] Before providing a detailed explanation of the antennas provided in the embodiments of this application, the application scenarios involved in the embodiments of this application will be described first.

[0121] The development of 5G (5th generation mobile communication technology) systems has met the growing communication needs of terminal devices. However, terrestrial mobile systems currently cover approximately 6% of the Earth's surface, equivalent to 20% of the land area. Based on this, global wireless communication coverage can be achieved using satellite communication methods. Satellites include geostationary orbit (GEO), medium Earth orbit (MEO), and low Earth orbit (LEO) satellites. The higher the satellite orbit, the larger the ground area it can cover; however, this also leads to increased communication latency and higher requirements for transmission and reception power.

[0122] Currently, traditional high-pass antennas supporting high-orbit satellite communication are single-port fed directional circularly polarized antennas. These require user alignment; that is, the terminal device needs to be aligned with the satellite to achieve satellite communication. Traditional high-pass antennas use single-port feeding to achieve high gain and directional circular polarization, resulting in a narrow beam and high gain, making them suitable for high-orbit satellite communication. However, due to their directional beam, the antenna coverage is low, and users need to align them for communication. Therefore, traditional high-pass antennas are not suitable for low-orbit satellite communication.

[0123] The aforementioned Low Earth Orbit (LEO) satellites can also be called low-Earth orbit satellites. A LEO satellite system can include multiple LEO constellations. An LEO constellation refers to a constellation of artificial satellites orbiting the Earth at a relatively low altitude. LEO constellations are close to the ground, have excellent signal quality, and possess advantages such as low power consumption, low latency, and fast response. They are commonly used for communication, resulting in strong signals, fast network speeds, and good voice quality. Multiple LEO satellites forming a constellation can achieve seamless full coverage of the globe or a designated area.

[0124] This solution provides an antenna for low-Earth orbit (LEO) satellite communication. The antenna features low gain and full space coverage. Terminal devices establish satellite communication with LEO satellites through this antenna, thereby reducing communication latency and lowering the requirements for antenna transmit and receive power. This reduces the posture requirements for users to use terminal devices for satellite communication and improves the efficiency and stability of satellite communication.

[0125] Next, we will conduct a theoretical analysis of the antenna structures that may be implemented in the terminal device. For example... Figure 2 As shown, Figure 2 This is a spherical spatial polarization distribution map provided in an embodiment of this application. Figure 2The polarization distribution of the terminal device in spherical space is shown. It is assumed that the electromagnetic waves transmitted in low-Earth orbit satellite communication are right-hand circularly polarized (RHCP). Since the terminal device is small in the Z-direction, it can be simply modeled as an idealized metallic plane, with the xoy plane representing the φ direction and the xoz or yoz plane representing the θ direction. In the xoy plane, the terminal device only has a linear polarization component in the φ direction. When θ approaches 90° (i.e., close to the xoy plane), because the antenna in the terminal device is linearly polarized in the xoy plane while the satellite is circularly polarized, the gain between the terminal device and the satellite decreases by approximately 3dB, or half. Here, dB represents a unit of measurement for antenna gain. In the region where θ is relatively small, the antenna on the plane has the potential to have both θ and φ polarization simultaneously, thus making it possible to achieve circular polarization and eliminate the 3dB loss. Based on this, the above... Figure 2 In a sphere, the antenna surface can be simply divided into the linearly polarized region (LP region) for antenna radiation and the circularly polarized region (CP region) where the antenna can potentially achieve circular polarization. It should be noted that while the CP region can theoretically achieve circular polarization, which specific regions can achieve circular polarization depends on the antenna design.

[0126] Traditional high-orbit satellite communication antennas are high-gain, narrow-beam antennas, but narrow beamwidths are detrimental to space beam coverage. Due to the presence of a metal ground plane in the terminal equipment, a single antenna cannot achieve complete space coverage, while multiple antennas introduce structural complexity. Therefore, this application designs two excitation elements based on a metal ground plane. By exciting through two feed ports and maintaining equal excitation current amplitudes, the phase difference between them is adjusted to achieve wide coverage with space beam steering, thereby reducing the complexity of the antenna design. Moreover, since this antenna provides space beam coverage, its gain does not need to be too high to communicate with low-orbit satellites.

[0127] Traditional array beam steering is achieved by adjusting the phase difference between the feed ports, which changes the array factor but does not alter the element radiation pattern; the nulls in the element radiation pattern become nulls in the array radiation pattern. In this application, however, the two feed ports share the metal ground plane of the terminal equipment. Under different phase differences, they excite different current modes, resulting in changes in the corresponding radiation patterns, thus achieving beam steering and overcoming the problem of fixed radiation nulls in traditional beam steering.

[0128] To better illustrate the spatial beam coverage capability of the antenna in this application, the following will first combine... Figure 3 The array beam of a traditional directional antenna is explained. Figure 3This is a schematic diagram of a conventional dipole two-element array provided in an embodiment of this application. The two dipole antennas (including dipole 1 and dipole 2) are excited by feed port 1 and feed port 2, respectively. Adjusting the phase difference between feed port 1 and feed port 2 allows for beam steering.

[0129] Regarding the above Figure 3 Simulations using traditional dipole two-element arrays can yield results such as... Figure 4 The radiation patterns of a conventional dipole two-element array under current excitation with different phase differences are shown. Figure 4 The radiation modes under different excitations are shown. Figure 4 Figure A in the diagram shows the radiation pattern when the two ports are in phase (phase difference of 0°). Figure 4 Figure B in the diagram shows the radiation pattern when the two ports are out of phase (180° phase difference). Gain, measured in dB (inverse proportional-logarithmic gain), is a unit of measurement used to represent the gain of an antenna. It is the gain value of an antenna's radiation capability in a specific direction relative to a standard reference antenna; the dB value determines the antenna's radiated power.

[0130] Depend on Figure 4 It can be seen that although the radiation pattern of a traditional dipole array can be steered by adjusting the phase difference, the radiation polarization remains linear, and the radiation nulls along the y-axis cannot be eliminated. The positions of the radiation nulls do not change, and the radiation pattern contains nulls. The nulls of the element pattern become the nulls of the array pattern. In other words, Figure 4 In diagram A, there is no radiation along the y-axis. Figure 4 The B-graph in the image shows no radiation in the y-axis direction, and the dipole array only produces linear polarization in the y-direction. In satellite communication, such an array loses 3dB gain due to linear polarization. Therefore, in this application, the antenna polarization in the x and y directions is excited by adjusting the phase difference between two ports on the metal floor of the terminal device. Compared to conventional dipole arrays, the antenna provided in this application excites different current modes on the same metal floor. Mode switching can achieve spatial beam coverage and form circular polarization in certain areas, thereby reducing polarization loss in satellite communication.

[0131] To address the high coverage requirements of terminal equipment in low-Earth orbit satellite communication, based on the aforementioned theoretical analysis, this application proposes a phase modulation method using dual feed ports and a shared metal ground plane to achieve antenna beam steering. Unlike traditional beam steering, this application utilizes a metal ground plane and designs two excitation elements on the plane containing the metal ground plane. By adjusting the phase difference between the two feed ports, the orthogonal modes of the metal ground plane are excited, overcoming the inherent radiation null point of traditional array beam steering. Beam steering is achieved through radiation mode steering, thereby realizing spatial beam coverage, improving spatial coverage, reducing the location requirements of terminal equipment during satellite communication, eliminating the need for user alignment, and improving communication efficiency.

[0132] This application provides an antenna for communicating with a low-Earth orbit satellite system. See also... Figure 5 , Figure 5 This is a schematic diagram of antenna 1 provided in an embodiment of this application. Figure 1 The antenna 1 includes: a dielectric substrate 10, a metal ground plane 20, a first excitation element, a second excitation element, a first feed assembly 50, and a second feed assembly 60; the metal ground plane 20 is attached to a first surface of the dielectric substrate 10; the first excitation element is disposed on a first side of the metal ground plane 20, and the second excitation element is disposed on a second side of the metal ground plane 20; the dimensions of the first excitation element and the second excitation element are related to the target frequency band; the inner conductor of the first feed assembly 50 is connected to the first feed point 311 of the first excitation element, and the outer conductor of the first feed assembly 50 is connected to the metal ground plane 20; the inner conductor of the second feed assembly 60 is connected to the second feed point 411 of the second excitation element, and the outer conductor of the second feed assembly 60 is connected to the metal ground plane 20; the first feed assembly 50 is used to provide a first excitation current to the first excitation element; the second feed assembly 60 is used to provide a second excitation current to the second excitation element; the metal ground plane 20 is used to achieve spatial directional coverage in the target frequency band by radiating beam steering under the action of the first excitation current and the second excitation current with different phase differences.

[0133] In one embodiment, a current in the metal floor can be excited by creating grooves in the metal floor 20. (The above...) Figure 5The first excitation element includes a first gap 312 and a first matching piece 313, with a first feed point 311 disposed on the first matching piece 313. The second excitation element includes a second gap 412 and a second matching piece 413, with the second feed point 411 disposed on the second matching piece 413. Specifically, the first gap 312 extends away from the first side; the first matching piece 313 is disposed on the second surface of the dielectric substrate 10 and close to the first side, used for impedance matching of the first gap 312 in the target frequency band; the projection of the first matching piece 313 on the metal ground plane 20 and the first region are located on opposite sides of the first gap 312; the second gap 412 extends away from the second side; the second matching piece 413 is disposed on the second surface and close to the second side, used for impedance matching of the second gap 412 in the target frequency band; the projection of the second matching piece 413 on the metal ground plane 20 and the second region are located on opposite sides of the second gap 412.

[0134] In some embodiments, the above Figure 5 The diagram also shows a first grounding plate 314 disposed on the second surface and near the first side, the projection of the first grounding plate 314 on the metal floor 20 overlapping with the first region, and a through hole connecting the first grounding plate 314 and the metal floor 20; the outer conductor of the first power supply assembly 50 is connected to the first grounding plate 314; and a second grounding plate 414 disposed on the second surface and near the second side, the projection of the second grounding plate 414 on the metal floor 20 overlapping with the second region, and a through hole connecting the second grounding plate 414 and the metal floor 20; the outer conductor of the second power supply assembly 60 is connected to the second grounding plate 414.

[0135] In some embodiments, the above Figure 5 The outer conductor of the first power supply component 50 is connected to the first area of ​​the metal floor 20 through the first grounding plate 314; the vertical distance between the first area and the first power supply point 311 is less than the first distance threshold; the outer conductor of the second power supply component 60 is connected to the second area of ​​the metal floor 20 through the second grounding plate 414; the vertical distance between the second area and the second power supply point 411 is less than the second distance threshold.

[0136] The above Figure 5The following is an example of a device where the gap (first gap 312 or second gap 412) is an L-shaped groove, the power supply assembly (first power supply assembly 50 or second power supply assembly 60) is a coaxial cable, the dielectric substrate 10 is made of fiber glass board (FR-4), the matching piece (first matching piece 313 or second matching piece 413) is a metal piece without through holes, and the grounding piece (first grounding piece 314 and second grounding piece 414) is a metal piece with through holes. The bottom surface of the dielectric substrate 10 is the first surface, the top surface of the dielectric substrate 10 is the second surface, the starting end of each gap is located at the center of its long side, and the two gaps are axially symmetrical. Specifically, the inner conductor of the first power supply assembly 50 is connected to the first power supply point 311, and the outer conductor of the first power supply assembly 50 is connected to the metal ground plane 20, forming the first power supply port. The inner conductor of the second power supply assembly 60 is connected to the second power supply point 411, and the outer conductor of the second power supply assembly 60 is connected to the metal ground plane 20, forming the second power supply port.

[0137] Grooves are cut into the metal floor 20 to create gaps, and power is supplied through two power supply ports loaded on the gaps to excite different current modes in the metal floor. Figure 5 Figure A shows a top view of antenna 1, with two L-shaped slots located at the center of the long side of metal floor 20, and two feed ports (including the first feed port and the second feed port) located on the long side of metal floor 20. Figure 5 Figure B in the diagram shows an enlarged view of the L-shaped slot in antenna 1, where l1 = 2.8 mm, l2 = 14.5 mm, l3 = 13.5 mm, l4 = 2.3 mm, and w1 = 1 mm. Figure 5 Figure C in the diagram is a partially enlarged view of antenna 1. The dielectric substrate of the antenna is FR4, where the relative permittivity ε of FR4 is... r =4.8, loss tangent tanδ =0.02, thickness h =0.5mm.

[0138] It should be noted that the above Figure 5 The dimensions of antenna 1 shown are merely illustrative and do not imply that the antenna 1 provided in this embodiment is limited to this. For example, the structure of the slot can be a straight slot, an arc slot, or a folded slot, etc. Moreover, given that the dimensions of the dielectric substrate and the target frequency band are determined, the specific length and width of the slot and the dimensions of the matching piece can be appropriately adjusted according to the simulation software used to simulate the antenna or the testing tools used to test the antenna. There are many possible combinations, and it is not limited to the above. Figure 5 The values ​​shown in the figure.

[0139] The above Figure 5The length of the L-shaped groove shown is l2 + l3 = 14.5 mm + 13.5 mm = 28 mm. The center frequency of the target frequency band is 1.5 GHz, and its wavelength in the dielectric substrate is [wavelength value missing]. λ / 4≈22.5mm, the length of the L-shaped groove is slightly greater than one-quarter of the wavelength of 1.5GHz on the dielectric substrate.

[0140] To make it easier to see the through holes in the dielectric substrate 10, Figure 5 The dielectric substrate 10 is transparent, and the metal ground plane 20 is located at the bottom of the dielectric substrate 10. As an example, the dimensions of the dielectric substrate 10 and the metal ground plane 20 can be 140mm × 70mm, that is, length l = 140mm and width w = 70mm. Figure 5 As shown in Figure B, on the top surface of the dielectric substrate 10, above the L-shaped groove, there are two metal plates. One metal plate has no through-hole and serves as a mating plate; the other metal plate is connected to the metal ground plane 20 through a through-hole and serves as a grounding plate. A coaxial cable is connected to these two metal plates. The outer conductor (outer core) of the coaxial cable is connected to the metal plate with the through-hole, which is equivalent to the outer conductor being connected to the metal ground plane 20. The inner conductor (inner core) of the coaxial cable is connected to the other metal plate without a through-hole (i.e., the mating plate) to excite current in the metal ground plane.

[0141] In some embodiments, by the above Figure 5 Figure A shows that the projection of the matching piece on the metal floor 20 overlaps with the gap.

[0142] Figure 5 Figure D shows the top surface of the dielectric substrate 10. Two metal plates are disposed on the first edge of the top surface of the dielectric substrate 10. One metal plate has no through-hole (i.e., a mating plate), and the other metal plate has a through-hole (i.e., a grounding plate). A metal ground plane 20 is attached to the bottom surface of the dielectric substrate 10. Figure 5 Figure E shows a metal floor 20. The metal floor 20 has two L-shaped grooves, and each L-shaped groove has a through hole on one side. The through hole on the metal floor 20 is connected to the grounding plate on the top surface through the dielectric substrate 10.

[0143] To make the through hole easier to see, such as Figure 6 As shown, Figure 6 This is a schematic diagram of antenna 1 provided in an embodiment of this application. Figure 2 , Figure 6 Figure A in the diagram shows a three-dimensional view of antenna 1. Figure 6 Figure B shows an enlarged view of the L-shaped slot in antenna 1. One of the two metal plates can be connected to the metal ground plane 20 through a metal through hole.

[0144] In this example, a metal plate connected to a through-hole in the metal ground plane 20 is provided. Connecting the outer conductor to the through-hole metal plate is equivalent to connecting the outer conductor to the metal ground plane 20. Thus, the connection points of both the outer and inner conductors are on the top surface of the dielectric substrate 10, without affecting the layout of the metal ground plane 20, thereby increasing the feasibility of antenna implementation. This example uses an L-shaped slot, which reduces the length of the groove in the y-direction on the metal ground plane 20, minimizing its impact on the overall structural orientation of the metal ground plane 20. The L-shaped slot and the through-hole-less metal plate serve as impedance matching elements, acting as a parallel inductor and a series capacitor, respectively. Adjusting the length of the L-shaped slot adjusts the inductance, and adjusting the size of the metal plate adjusts the capacitance, thereby achieving impedance matching at the target frequency band and reducing energy loss during energy radiation after connection to a coaxial cable.

[0145] In some embodiments, such as Figure 7 As shown, Figure 7 These are schematic diagrams of different forms of antenna 1 provided in the embodiments of this application. Figure 1 It should be understood that the antenna 1 provided in this embodiment may also have other slot forms. For example... Figure 7 As shown in Figure A, the slot structure can be a straight line structure; as... Figure 7 Figure B in the middle and Figure 7 As shown in Figure C, the slit structure can be a polygonal structure; such as Figure 7 As shown in Figure D, the slot structure can be an arc-shaped structure. This application does not limit the slot structure, as long as it can excite a current on the metal floor.

[0146] For example, taking the first excitation element and the second excitation element as gaps, the structure of the two gaps provided in this embodiment can be axially symmetrical on the metal floor 20, such as... Figure 5 and Figure 6 The L-shaped groove shown in the figure is symmetrical, such as Figure 7 The A diagram shows an axisymmetric straight groove, such as... Figure 7 Figure B in the middle and Figure 7 The C-shaped groove shown in the diagram is an axisymmetric polygonal groove, such as... Figure 7 The D-shaped groove shown in the diagram is axially symmetrical. The two gaps provided in this embodiment can also be centrally symmetrical on the metal floor 20, such as... Figure 8 The L-shaped groove shown in Figure A is centrally symmetrical, as... Figure 8 Figure B in the middle and Figure 8 The C-shaped groove shown in the diagram is a centrally symmetrical polygonal groove, such as... Figure 8 The D-shaped groove in the diagram is a centrally symmetrical arc shape.

[0147] In some embodiments, the metal floor 20 has a rectangular structure, and the two gaps can be located on the two long sides of the metal floor 20, or the two gaps can be located on the two short sides. The starting ends of the two gaps can be located at the center of the two sides; or the starting ends of the two gaps can be centrally symmetrical.

[0148] For example, taking the first excitation element and the second excitation element as a slot, the slot position in the antenna 1 provided in this application embodiment can be not only in the middle of the long side, but also at other positions on the long side. Figure 5 and Figure 6 Taking the two mirrored L-shaped grooves as an example, in Figure 5 and Figure 6 In the middle, the two L-shaped grooves are located at the center of the long side. Figure 9 In Figure A, one of the two L-shaped grooves is located slightly above the long side, for example, at a distance of one threshold from the center, and facing the first direction. The other is located slightly below the long side, also at a distance of one threshold from the center, and facing the second direction, which is opposite to the first direction. The positions of the two L-shaped grooves on the long side can be centrally symmetrical. Figure 9 In diagram B, both L-shaped grooves are located slightly above the long side, for example, at a distance of two from the center. The positions of the two L-shaped grooves on the long side can be axially symmetrical. Figure 9 In Figure C, both L-shaped grooves are located slightly below the long side, for example, at a distance of three from the center. The positions of the two L-shaped grooves on the long side can be axially symmetrical.

[0149] Understandably, for Figure 7 Figure A in the middle Figure 7 Figure B in the middle Figure 7 Figure C in the middle and Figure 7 In diagram D, the two grooves on the metal floor 20 can be located one slightly above the long side and the other slightly below the long side, as described above. Figure 9 Figure A. It can also be located slightly above the longer side, as shown above. Figure 9 Figure B in the diagram. It can also be located slightly below the longer side, as shown above. Figure 9 Figure C is shown in the diagram. Further details regarding the embodiments described in this application will not be repeated here.

[0150] Of course, for Figure 8 Figure A in the middle Figure 8 Figure B in the middle Figure 8 Figure C in the middle and Figure 8In diagram D, the two L-shaped grooves on the metal floor 20 can be positioned such that one is located slightly above the long side (e.g., a distance of four from the center and facing the first direction), and the other is located slightly below the long side (e.g., a distance of four from the center and facing the first direction). The positions of the two L-shaped grooves on the long side can be centrally symmetrical. Figure 9 As shown in Figure D. It can also be located slightly above the long side, as described above. Figure 9 Figure B in the diagram. It can also be located slightly below the longer side, as shown above. Figure 9 Figure C is shown in the diagram. Further details regarding the embodiments described in this application will not be repeated here.

[0151] The welding position of the outer conductor of the coaxial cable in the antenna 1 provided in this embodiment can include the following two methods: First, the welding position of the outer conductor of the coaxial cable can be on the top surface of the dielectric substrate 10. A metal plate connected to a through hole in the metal ground plane 20 is provided on the top surface, and the outer conductor of the coaxial cable is welded to this metal plate with the through hole. In this method, the connection points of the outer and inner conductors of the coaxial cable are both on the top surface of the dielectric substrate 10, which does not affect the layout of the metal ground plane 20 and improves the feasibility of antenna implementation. Second, the welding position of the outer conductor of the coaxial cable can be on the metal ground plane 20 of the dielectric substrate 10. This eliminates the need for a metal plate connected to the through hole in the metal ground plane 20; a welding area can be defined on the metal ground plane 20, and this welding area can be located near the gap. For example... Figure 10 As shown in Figure A, the welding area can be the projection area of ​​a metal sheet with through holes onto the metal ground plane 20, and the outer conductor of the coaxial cable is welded to the welding area. This method eliminates the need for a metal sheet on the top surface of the dielectric substrate 10 and for through holes inside the dielectric substrate 10, simplifying antenna design.

[0152] It should be noted that the slot structure, the location of the slot, and the welding position of the outer conductor of the coaxial cable in the antenna 1 provided in this embodiment are not limited to those described above. Figures 5-9 The two slot structures in antenna 1 can be identical or different. The outer conductors of the two coaxial cables in antenna 1 can both be soldered on the top surface of the dielectric substrate 10, or one can be on the top surface of the dielectric substrate 10 and the other on the metal ground plane 20 of the dielectric substrate 10. In other words, antenna 1 in this embodiment can be a combination of various forms, such as... Figure 10As shown in Figure B, an L-shaped slot and an arc-shaped slot are provided on the metal ground plane 20 of antenna 1. The L-shaped slot and the arc-shaped slot are located on the two long sides, respectively, and their positions on the long sides are axially symmetrical. The L-shaped slot is located slightly above the long side, and the arc-shaped slot is located slightly below the long side. The outer conductor of the coaxial cable of the L-shaped slot is soldered to the soldering area of ​​the metal ground plane 20, and the outer conductor of the coaxial cable of the arc-shaped slot is soldered to a metal sheet on the top surface of the dielectric substrate 10. This metal sheet is connected to a through hole in the metal ground plane 20.

[0153] It should be noted that changes to the slot structure of antenna 1, such as changing from an L-shaped slot to an arc-shaped slot, require fine-tuning of the slot length and the size of the matching piece to achieve impedance matching in the target frequency band. Similarly, changes to the slot positions of antenna 1, such as changing from both being located at the center of the long side to one being located slightly above the long side and the other slightly below, also require fine-tuning of the slot length and the size of the matching piece to achieve impedance matching in the target frequency band. These details will not be elaborated further in this embodiment.

[0154] In some embodiments, a first groove corresponding to the structure and position of the first gap 312 may be formed on the dielectric substrate 10; and / or, a second groove corresponding to the structure and position of the second gap 412 may be formed on the dielectric substrate 10.

[0155] In this embodiment, slots corresponding to the structure and position of the gaps can also be formed on the dielectric substrate, which increases the diversity of antenna manufacturing processes and the diversity and richness of antenna structures.

[0156] Next, regarding the above Figure 5 or Figure 6 The simulation results and actual measurement results of the provided antenna 1 are analyzed.

[0157] The above Figure 5 or Figure 6 The provided antenna 1 has two L-shaped slots on the metal ground plane 20 of its dielectric substrate 10. These two L-shaped slots are axially symmetrical and located at the center of their long sides. The outer conductors of two coaxial cables are connected to a metal plate with through holes. Taking a target frequency band center frequency of 1.5 GHz as an example... Figure 11 This is the current distribution diagram of antenna 1 at a frequency of 1.5 GHz, shown in vector form Jsurf (A / m). Figure 11 Figure A shows the current distribution of antenna 1 under common-mode (CM) excitation. Common-mode means that the phase difference between the two L-shaped slots is 0°, and the two L-shaped slots are in phase. Under CM excitation, the main direction of the radiated current of the metal ground plane is the x-direction, as shown in Figure A. Figure 11 The diagram in Figure A shows the direction of the current along the x-axis. According to... Figure 11From the current distribution in diagram A, we can deduce that the polarization direction of antenna 1 is x-polarization, as shown below. Figure 12 Figure A in the diagram shows the radiation pattern corresponding to the CM excitation.

[0158] In some embodiments, the first current distribution and the second current distribution on the metal floor are orthogonal to each other, such that the radiation null point of the antenna under common-mode excitation is complementary to the radiation null point under differential-mode excitation. The first current distribution refers to the current distribution on the metal floor when the first excitation current and the second excitation current are common-mode, and the second current distribution refers to the currents on the metal floor being orthogonal when the first excitation current and the second excitation current are differential-mode.

[0159] Figure 11 Figure B shows the current distribution of antenna 1 under differential mode (DM) excitation. Differential mode refers to a 180° phase difference between the two L-shaped slots, meaning the two slots are out of phase. Under DM excitation, the dominant direction of the radiated current from the metal ground plane is the y-direction. Although the y-direction currents on the two short sides of the metal ground plane are out of phase, as shown in Figure B... Figure 11 The diagram in Figure B shows the current direction along the y-axis. However, due to the large spatial distance, the currents along the y-axis do not cancel each other out; therefore, the radiation along the x-axis superimposes. According to... Figure 11 From the current distribution in diagram B, it can be inferred that the polarization direction of antenna 1 is y-polarized, as shown below. Figure 12 Figure B in the diagram shows the radiation pattern corresponding to the DM excitation. Figure 12 As can be seen from Figure B, the radiation from antenna 1 is superimposed along the x-direction.

[0160] The above Figure 11 Figure A in the diagram shows the radiation current along the x-direction under CM excitation. Figure 11 Figure B illustrates the radiated current along the y-axis under DM excitation. This means that at the two feed ports on the metal ground plane, CM and DM can excite different modes: y-polarized current and x-polarized current, respectively. Thus, two orthogonal modes of ground current are successfully excited. CM excitation results in stronger radiation along the y-axis, while DM excitation results in stronger radiation along the x-axis. In other words, the radiation null point under CM excitation is where the radiation is stronger under DM excitation, and vice versa. The main lobe and radiation null points of the radiation patterns under CM and DM excitation are complementary, which is beneficial for the antenna to achieve full-space beam coverage under excitation with different phase differences.

[0161] The antenna 1 provided in this embodiment differs from traditional beam steering, such as... Figure 3 and Figure 4The conventional dipole array shown in the diagram cannot eliminate its radiation null point. In this embodiment, the metal ground plane of the terminal device is utilized. By adjusting the phase difference between the two feed ports, the orthogonal mode of the metal ground plane can be excited, as described above. Figure 11 and Figure 12 As shown, this eliminates the inherent radiation null point of traditional array beam steering. This antenna features a wide beam and high coverage, making it suitable for low-Earth orbit satellite communications.

[0162] like Figure 13 As shown, Figure 13 The active return loss (S) at the dual-feed port of antenna 1 under eight phase differences is shown. 11 Phase difference The angles are 0°, 45°, 90°, 135°, 180°, 225°, 270°, and 315°, respectively. Typically, antennas are passive devices. 11 This refers to a situation where one feeder port receives energy, while the other feeder port is connected to a matched load (i.e., not operating). In this example, "active" means there is coupling between the two feeder ports; the active S of a single feeder port... 11 It will be affected by the S of another power supply port. 12 Impact, and S 12 It includes the phase of the feed port; therefore, phase changes will cause S 11 Change, active S 11 =S 11 +S 12 . Figure 13 The horizontal axis represents frequency (GHz), and the vertical axis represents active S. 11 (dB). Figure 13 The active S of antenna 1 is shown. 11 Simulation results show that the active impedance in this example (i.e., S) 11 The phase difference between the feed ports will change. Under eight phase conditions, the active S 11 The signal strength remains below -10dB within the 1.47GHz-1.53GHz range, meeting the antenna design requirements. In other words, antenna 1 has a 60MHz communication bandwidth, which is sufficient for satellite communication needs.

[0163] The above Figure 11 and Figure 12This paper demonstrates antenna radiation modes under two discrete phase difference (CM and DM) conditions. Since the two L-shaped slots located on the metal ground plane can radiate spatial beams of different intensities at the same spatial point with different phase differences, this embodiment of the application achieves gain improvement by continuously adjusting the phase difference between the feed ports. In practical applications, discrete phase differences can be used to achieve beamforming. In this example, a discrete phase difference of 45° is used to feed the two feed ports to improve the antenna beam coverage.

[0164] The above assumption is that the electromagnetic waves transmitted in satellite communication are RHCP. Therefore, during communication between the terminal device and the satellite, the RHCP gain of the terminal device's antenna is of concern. For example... Figure 14 As shown, Figure 14 This is a schematic diagram of the two-dimensional radiation modes of the dual-feed port of antenna 1 provided in this application, with right-hand gain under eight phase differences. Figure 14 The two feed ports are shown in different At that time, the two-dimensional radiation mode of RHCP, Figure 14 The horizontal axis represents θ (deg), the vertical axis represents φ (deg), and the phase diversity (PD) is 0°, 45°, 90°, 135°, 180°, 225°, 270°, and 315°, respectively. Figure 14 The RHCP gain gradient value is also shown to the right of each two-dimensional radiation mode. Figure 14 Figure A in the diagram shows Two-dimensional radiation mode at time; Figure 14 Figure B in the diagram shows Two-dimensional radiation mode at time; Figure 14 Figure C in the diagram shows Two-dimensional radiation mode at time; Figure 14 The D diagram in the figure shows Two-dimensional radiation mode at time; Figure 14 The E diagram in the figure shows Two-dimensional radiation mode at time; Figure 14 The F diagram in the figure shows Two-dimensional radiation mode at time; Figure 14 The G diagram in the figure shows Two-dimensional radiation mode at time; Figure 14 The H diagram in the figure shows The two-dimensional radiation mode at that time. Figure 14 As can be seen from the eight figures, the position of the main beam of antenna 1 varies with... The phase difference varies depending on the location, and can be adjusted by changing the phase difference between the two feed ports. This causes the radiation pattern to shift.

[0165] Based on the above Figure 14Each spatial point (θ, φ) corresponds to eight RHCP gain values. For each spatial point (θ, φ), the maximum value among the eight RHCP gains is extracted and combined into a single value. Figure 15 Figure A in the diagram. Figure 15 Figure A in the diagram shows the maximum RHCP gain at each spatial point; that is, the gain at each spatial point is the maximum gain across all eight figures. Figure 15 Figure A in the diagram shows the combined radiation pattern of the RHCP gain. Figure 15 In Figure A, the area within the dashed circle represents a gain less than -2 dBic. Figure 15 As shown in Figure A, there are no radiation null points throughout space, and the RHCP gain in most areas reaches -2dBic or greater. This means that users can directly connect with low-Earth orbit satellites from most angles during communication, establishing stable communication without requiring the user to align with the satellites or maintain a stable attitude. This also demonstrates that the embodiments of this application can achieve space beam coverage by adjusting the phase difference between the two feed ports.

[0166] It should be noted that the radiated electromagnetic wave at each spatial point has not only right-hand circular polarization (RHCP) gain but also left-hand circular polarization (LHCP) gain. When the LHCP gain at a spatial point equals the RHCP gain, it indicates that the radiated electromagnetic wave at that point is linearly polarized. When the RHCP gain at a spatial point is greater than the LHCP gain, it indicates that the radiated electromagnetic wave at that point is mainly an RHCP wave. When the RHCP gain at a spatial point is much greater than the LHCP gain, it indicates that the radiated electromagnetic wave at that point is an RHCP wave. When the RHCP gain at a spatial point is less than the LHCP gain, it indicates that the radiated electromagnetic wave at that point is mainly an LHCP wave. When the RHCP gain at a spatial point is much less than the LHCP gain, it indicates that the radiated electromagnetic wave at that point is an LHCP wave.

[0167] Based on this, for any spatial point A, the maximum RHCP gain of spatial point A has a corresponding target phase difference. The LHCP gain of spatial point A under this target phase difference is extracted. This operation is performed for each spatial point to obtain the LHCP gain. Figure 15 Figure B in the diagram. Figure 15 Figure B in the diagram is related to... Figure 15 Figure A shows the LHCP gain corresponding to the RHCP gain, i.e., the cross-polarization of the combined RHCP gain. In this example... Figure 15 The B diagram in the image is only for analyzing whether the region is linearly or circularly polarized.

[0168] By comparison Figure 15 Figure A in the middle and Figure 15In Figure B, it can be observed that in the region approximately 80° < θ < 100°, the LHCP gain and RHCP gain are roughly equal, indicating linear polarization in this region. In the regions approximately 20° < θ < 80° and 100° < θ < 160°, the RHCP gain in some sub-regions is significantly higher than the LHCP gain, indicating circular polarization in these regions. (This is consistent with the above...) Figure 2 The theoretical analysis is consistent. Approximately in the regions where θ < 15° and θ > 165°, since the LHCP gain and RHCP gain are almost equal, these regions are linearly polarized. This is determined by the antenna design. When When the value is zero, the RHCP gain and LHCP gain are at their maximum in this region. (Combined with the above...) Figure 11 As shown in Figure A, when the two feed ports are in common mode (phase difference 0°), the current in the metal floor is only in the x-direction; therefore, this region is the LP region. It should be noted that this region occupies a relatively small proportion because when θ = 0°, different... The value corresponds to the same point on the sphere, i.e., the pole. Therefore, it can be seen that by exciting different current modes on the same metal ground plane, mode switching can achieve the technical effect of RHCP covering a larger area.

[0169] Based on the above Figure 15 Analysis shows that the linear polarization regions are approximately θ < 15°, θ > 165°, and 80° < θ < 100°. Although antenna 1 cannot achieve circular polarization in its linear polarization region, its linear polarization gain is relatively high, reaching 5 dBic. Even if the linear polarization gain is evenly divided into RHCP and LHCP gains, and the circular polarization gain is reduced by 3 dB, the final circular polarization gain still meets communication standards. For example, the RHCP gain is approximately 2 dBic, and the corresponding LHCP gain is approximately 2 dBic.

[0170] The antenna provided in this embodiment has two feed ports sharing the same metal ground plane. By adjusting the phase difference between the two feed ports, different current modes can be excited in the metal ground plane. Circular polarization can be achieved in the 20°<θ<80° and 100°<θ<160° regions. Even in the θ<15°, θ>165°, and 80°<θ<100° regions, which are linearly polarized, the linear polarization gain is high, and the minimum gain requirement for communication is still met even after the gain loss from circular polarization. Therefore, the antenna 1 provided in this embodiment is a wide-beam antenna, which can establish satellite communication without user alignment, thus improving the efficiency of satellite communication. Moreover, since the wide-beam antenna has comprehensive coverage capability, even if the low-Earth orbit satellite moves, the satellite communication quality between the low-Earth orbit satellite and the antenna will not be significantly affected, thus improving the stability of satellite communication.

[0171] It should be noted that the above describes feeding the two feed ports with a discrete phase difference gradient of 45°. It can be understood that the discrete phase difference gradient can also be 30°, corresponding to PD values ​​of 0°, 30°, 60°, 90°, 120°, 150°, 180°, 210°, 240°, 270°, 300°, and 330°. The discrete phase difference gradient can also be 90°, corresponding to PD values ​​of 0°, 90°, 180°, and 270°. This application does not limit the embodiments in this regard.

[0172] The above Figure 11 and Figure 12 The antenna radiation modes under two discrete phase differences (0° and 180°) are demonstrated. The phase difference between the two feed ports of the antenna can be adjusted to 0° and 180° respectively to obtain the RHCP gain values ​​at each spatial point (θ, φ) at 0° and 180°. For each spatial point (θ, φ), the maximum of the two RHCP gains is selected and combined to form a combined radiation pattern of the maximum RHCP gain for each spatial point. Typically, in low-Earth orbit satellite communication, an RHCP gain above -2 dBic is sufficient to maintain communication. Based on this, statistical analysis of the above combined radiation patterns shows that the region with an antenna RHCP gain greater than -2 dBic can cover approximately 60% of the space.

[0173] The above Figure 14 and Figure 15 The example further demonstrates antenna radiation modes under eight discrete phase differences (0°, 45°, 90°, 135°, 180°, 225°, 270°, and 315°). The area where the antenna RHCP gain is greater than -2 dBic can cover approximately 80% of the space. In practical applications, communication with low-Earth orbit satellites can be achieved by adjusting the phase differences of the dual-feed ports to 0°, 45°, 90°, 135°, 180°, 225°, 270°, or 315°. The preset phase differences in this example include 0°, 45°, 90°, 135°, 180°, 225°, 270°, and 315°. The coverage rate under this adjustment method is higher than that of the other two phase differences, thus improving communication quality.

[0174] Understandably, in practical applications, current excitation of discrete phase differences can be achieved using phase shifters. The smaller the gradient of the discrete phase difference, the more precise the phase shifter, and the higher the requirements for all aspects of the phase shifter. Therefore, a balance needs to be struck between the gradient of the discrete phase difference and the precision of the phase shifter. Specifically, the smaller the gradient of the discrete phase difference, the greater the coverage and the higher the communication quality. The larger the gradient of the discrete phase difference, the simpler the adjustment method and the lower the requirements for the phase shifter.

[0175] In this embodiment, considering the precision of the phase shifter, a 180° gradient can be set to achieve communication with low-Earth orbit satellites via CM and DM; alternatively, a 45° gradient can be set to improve the coverage of the wide-beam antenna and further enhance communication quality. Of course, in practical applications, other gradients can be set, such as 90° or 60°, etc. This embodiment does not limit the application in this respect. This embodiment is merely an example using 180° and 45° phase difference gradients and does not imply that this application is limited to these.

[0176] As mentioned above Figure 14 As shown, the radiation mode of antenna 1 varies in different... The value changes, achieving near-full spatial coverage. To more intuitively see the effect of each spatial angle (i.e., spatial point) at the point of maximum RHCP gain... This example calculates the phase difference at each spatial point (θ, φ) when the maximum RHCP gain is achieved, resulting in a phase distribution diagram, as shown below. Figure 16 As shown, Figure 16 Is with Figure 15 The phase distribution diagram corresponding to Figure A in the middle. Figure 16 It shows the relationship with Figure 15 The RHCP gain corresponding to Figure A in the middle is Numerical values. It is evident that different spatial angles (i.e., spatial points) require different values. Only then can the maximum RHCP gain be achieved. Figure 16 It can be seen that each discrete phase difference contributes, but the proportions they each account for are different.

[0177] It should be noted that the embodiments of this application utilize a phase shifter to excite the two feed ports of the antenna with a phase difference. A smaller discrete phase difference gradient results in greater coverage, but also places higher demands on the various performance indicators of the phase shifter. Therefore, a balance needs to be found between the discrete phase difference gradient and the coverage. For example, a coverage rate with a discrete phase difference gradient of 45° will be greater than that with a discrete phase difference gradient of 90°. Based on the above... Figure 16 It can be seen that when the discrete phase difference gradient is 45°, the coverage can reach 80%, which can meet the communication requirements. The phase distribution diagram can provide theoretical support for the specific implementation of phase difference in subsequent practical communication.

[0178] It should be noted that the above analysis assumes that the electromagnetic waves transmitted in satellite communication are RHCP. Alternatively, it can be assumed that the electromagnetic waves transmitted in satellite communication are LHCP. In this case, the maximum value of the eight LHCP gain values ​​corresponding to each spatial point (θ, φ) is extracted to obtain the combined LHCP gain pattern. Furthermore, the phase difference corresponding to the maximum LHCP gain at each spatial point (θ, φ) can be statistically analyzed to obtain the phase distribution pattern.

[0179] Based on the above Figures 14-16 This application embodiment also provides a spatial coverage curve of the right-hand rotation gain of antenna 1, such as... Figure 17 As shown, Figure 17 The cumulative distribution function (CDF) of gain coverage after phase modulation of antenna 1 is shown. Figure 17 It can be seen that the area with antenna RHCP gain greater than -2dBic covers 80% of the space, and the area with antenna RHCP gain greater than -4dBic covers 99% of the space.

[0180] Figure 17 The spatial coverage of antenna 1 provided in this embodiment is shown for easy comparison. Figure 17 The spatial coverage of a conventional circularly polarized antenna for communication with high-orbit satellites is also shown, with the horizontal axis representing gain RHCP (dBic) and the vertical axis representing coverage rate. Figure 17 It can be seen that the spatial coverage of traditional high-pass antenna 1 and traditional high-pass antenna 2 is very limited because they are high-gain directional antennas with narrow beams, suitable for high-orbit satellites. In low-orbit satellite communication scenarios, antennas require greater coverage. The antenna provided in this application embodiment achieves high coverage by adjusting the phase difference between the two feed ports, and its RHCP gain exceeds -2dBic, achieving 80% coverage in areas where it can reach 80%. In contrast, traditional high-pass antenna 1 and traditional high-pass antenna 2 can only achieve 40% or lower coverage when the gain exceeds -2dBic. Therefore, the high-coverage antenna provided in this application embodiment is suitable for scenarios where terminal devices are directly connected to low-orbit satellites, improving the efficiency and stability of satellite communication.

[0181] This application provides a dual-feed-port metallic-ground antenna for low-Earth orbit satellite communication. By adjusting the phase difference between the two feed ports of the antenna, different current modes are excited on the metallic ground, thereby achieving beam steering. This antenna can achieve a combined radiation pattern with near-full-space coverage, as described above. Figure 15 As shown. Among them, the active S of antenna 1 11 The operating frequency band that meets the -10dB impedance requirement is 1.47GHz to 1.53GHz, which can cover a bandwidth of 60MHz, as mentioned above. Figure 13 As shown. Furthermore, the region where this antenna can achieve a gain of -2dBic reaches 80%, as mentioned above. Figure 17 As shown.

[0182] Next, we will introduce the probability of communication interruption during the communication process, namely the communication interruption probability P. out =(1-p) NWhere p is the probability that the antenna gain is higher than the minimum gain required for communication at a random spatial angle (i.e., any spatial point), and N is the number of low-Earth orbit (LEO) satellites available for communication. Typically, in LEO satellite communication, an RHCP gain of -2 dBic or higher is sufficient to maintain communication; that is, an RHCP gain exceeding -2 dBic is sufficient for communication with LEO satellites. For example... Figure 18 As shown, Figure 18 This is a schematic diagram of satellite communication provided in an embodiment of this application. The satellites include high-orbit (GEO), medium-orbit (MEO), and low-orbit (LEO) satellites. Since the relative positioning between the LEO satellites and the terminal equipment is unknown, Figure 17 The area shown where the antenna RHCP gain is greater than -2 dBic covers 80% of the space; therefore, p = 0.8, meaning the terminal device has an 80% probability of communicating with a low-Earth orbit (LEO) satellite. In LEO satellite communication, more than one satellite is typically observed. Under the condition of a single LEO satellite, P... out =0.2; Under the condition of two low-Earth orbit satellites, P out =0.04; Under the condition of three low-Earth orbit satellites, P out =0.008, which greatly improves the stability of satellite communication, and users no longer need to manually search for satellite positions, thus improving the efficiency of satellite communication. When there are multiple low-Earth orbit satellites in the user's environment, the user can achieve stable satellite communication without adjusting their posture.

[0183] like Figure 19 As shown, Figure 19 This is a schematic diagram of the physical structure of antenna 1 provided in an embodiment of this application. This physical structure diagram corresponds to the above-mentioned Figure 5 and Figure 6 , Figure 19 Figure A in the above corresponds to the above Figure 5 Figure E in the middle, Figure 19 Figure B in the above corresponds to the above. Figure 5 The D diagram in the image. Figure 19 The central antenna is an L-shaped slot. Figure 19 The L-shaped slot is fed using a coaxial cable as the feed assembly. The inner core of the coaxial cable is connected to a matching plate (i.e., a metal plate without through holes), while the outer core is connected to a metal plate with through holes. The welding positions of both the inner and outer cores are located on the top surface of the dielectric substrate, without affecting the layout of the metal ground plane. The S-parameters and radiation pattern of the antenna are measured in an anechoic chamber. The actual test environment corresponding to the anechoic chamber is as follows: Figure 20 As shown. Figure 20 Figure A in the diagram shows an overall overview of the actual antenna testing environment. Figure 20Figure B in the figure shows a partial view of the actual antenna test environment, which includes a receive antenna, the antenna as proposed in this application, and a metal cylinder that provides support.

[0184] In combination with the above Figure 13 and against Figure 19 The actual test of the antenna shown is as follows: Figure 21 As shown, Figure 21 This is a comparison diagram of the actual test and simulation return loss of antenna 1 provided in the embodiments of this application. Figure 21 The simulation and measurement S-parameters are given, with the horizontal axis representing frequency (GHz) and the vertical axis representing S-parameters (dB). Simulation S-parameters include S11 and S21, while measured S-parameters include S11, S22, and S21. Figure 12 It can be seen that in the frequency band of 1.45GHz-1.55GHz, the measured curves and simulated curves of S-parameters are very close.

[0185] In combination with the above Figure 15 and against Figure 19 The actual test of antenna 1 shown is as follows: Figure 22 As shown, Figure 22 This is a schematic diagram of the phase distribution of the antenna 1 provided in the embodiments of this application during actual testing. Figure 22 Figure A in the diagram shows the combined radiation pattern measured in practice, i.e., the combined radiation pattern of the RHCP gain. Figure 22 Figure B in the diagram shows Figure 22 Figure A shows the LHCP gain corresponding to the RHCP gain, i.e., the cross-polarization of the combined RHCP gain. (Comparison) Figure 22 Figure A in the middle and Figure 15 Figure A in the diagram, and the comparison Figure 22 Figure B in the middle and Figure 15 Figure B shows that the test radiation pattern and the simulation results are generally consistent, but there are slight differences in a few areas. Since the actual test is an omnidirectional radiation pattern, and the presence of a metal cylinder in the actual test environment affects the radiation pattern, a slight error occurs between the test and simulation radiation patterns, but this does not affect the overall analysis results.

[0186] In combination with the above Figure 16 and against Figure 19 The actual test of antenna 1 shown is as follows: Figure 23 As shown, Figure 23This is the combined gain radiation pattern of antenna 1 provided in the embodiment of this application, which is the actual test result. The horizontal axis is the gain RHCP (dBic), and the vertical axis is the coverage rate. Figure 23 Is with Figure 22 The phase distribution diagram corresponding to Figure A in the middle. Figure 23 It shows the relationship with Figure 22 The RHCP gain corresponding to Figure A in the middle is Numerical value. Basically related to Figure 16 The theoretical analysis results are consistent; different spatial angles (i.e., spatial points) require different... Only then can the maximum RHCP gain be achieved.

[0187] In combination with the above Figure 17 and against Figure 19 The actual test of antenna 1 shown is as follows: Figure 24 As shown, Figure 24 This is a comparison chart of the actual test and simulation coverage of antenna 1 provided in the embodiments of this application. Figure 24 The figure shows the coverage curve obtained from the simulation of antenna 1, as well as the coverage curve obtained from the simulation of antenna 1. Figure 19 The coverage curve shown is obtained after actual testing of antenna 1. Figure 24 It can be seen that the curves of the two are basically the same.

[0188] above Figures 5-24 Antenna 1 with a slot located on the long side of the metal ground plane 20 is described. In fact, the slot can also be located on the short side of the metal ground plane 20. The structure of the slot located on the short side can be as follows: Figures 7-10 The slots shown include straight slots, L-shaped slots, arc-shaped slots, and zigzag slots. The slots can be located in the middle of the short side or at other locations on the short side. The two slots on the metal ground plane 20 can be axially symmetrical or centrally symmetrical. The welding position of the outer conductor of the coaxial cable in the antenna can be on the metal ground plane 20 of the dielectric substrate 10, or it can be welded to a metal sheet with through holes on the top surface of the dielectric substrate 10. This application embodiment does not limit the slot structure, slot position, or welding method of the outer conductor of the coaxial cable located on the short side of the metal ground plane 20, as long as current can be excited on the metal ground plane 20. For details, please refer to the above description of antenna 1, which will not be repeated here.

[0189] like Figure 25 As shown, Figure 25 A schematic diagram of antenna 2 is provided for an embodiment of this application. Figure 25 The following example illustrates the process: two L-shaped grooves are located at the center of the short side of the metal floor 20, the two L-shaped grooves are axially symmetrical, and the outer conductor of the coaxial cable is welded to a metal sheet with through holes. Figure 25 Figure A in the diagram shows a three-dimensional view of antenna 2. Figure 25Figure B in the figure shows a top view of antenna 2. Both L-shaped slots are located at the center of the short side of the metal ground 20, and both feed ports (including the first feed port and the second feed port) are located on the short side of the metal ground 20.

[0190] right Figure 25 The simulation is performed using antenna 2 shown in the figure, taking a target frequency band center frequency of 1.5 GHz as an example. Figure 26 This is a current distribution diagram of antenna 2 at a frequency of 1.5 GHz, shown as surface current density (Jsurf), in amperes per meter (A / m). Figure 26 Figure A shows the current distribution of antenna 2 under common-mode (CM) excitation. Common-mode refers to a phase difference of 0° between the two L-shaped slots. Under CM excitation, the radiated current of the metal ground plane has both x and y directions. Figure 26 The current distribution in diagram A is as follows: Figure 27 Figure A in the diagram shows the radiation pattern corresponding to the CM excitation.

[0191] Figure 26 Figure B in the diagram shows the current distribution of antenna 2 under differential mode (DM) excitation. Differential mode refers to a 180° phase difference between the two L-shaped slots. Under DM excitation, the radiated current from the metal ground plane has both x and y directions. Figure 26 The current distribution in diagram B, as shown Figure 27 Figure B in the diagram shows the radiation pattern corresponding to the CM excitation.

[0192] With the above Figure 11 and Figure 12 The current distribution and radiation pattern of antenna 1 are similar to those shown. The current in the metal ground plane of antenna 2 also has two orthogonal modes. However, unlike antenna 1, the orthogonal modes excited by the common mode and differential mode of antenna 2 both have current in the x and y directions. Figure 27 The radiation patterns of the two modes are shown, by Figure 27 It can be seen that the radiation patterns of the two modes can effectively complement each other. Antenna 2 can also achieve full space coverage like antenna 1, and the spatial coverage of antenna 1 and antenna 2 is basically the same.

[0193] In this embodiment, the metal ground plane of the terminal device is utilized. By adjusting the phase difference between the two feed ports, the orthogonal mode of the metal ground plane can be excited, as described above. Figure 26 and Figure 27 As shown, this eliminates the inherent radiation null point of traditional array beam steering. This antenna features a wide beam and high coverage, making it suitable for low-Earth orbit satellite communications.

[0194] Based on antenna 1 and antenna 2 provided in the embodiments of this application, and in conjunction with the above... Figure 17The spatial coverage of the right-hand rotation gain of antennas 1 and 2 is explained. For example... Figure 28 As shown, Figure 28 This is a spatial coverage curve of the right-hand rotation gain of antenna 1 and antenna 2 provided in the embodiments of this application. To facilitate comparison of the beneficial effects of the antennas provided in the embodiments of this application on spatial coverage, Figure 28 The diagram also shows a switch antenna with two feed ports and a common-mode (CM) antenna with two feed ports. Although the switch antenna has two feed ports, these two feed ports switch operation, meaning they do not feed simultaneously. The common-mode antenna also has two feed ports, but they operate in phase.

[0195] exist Figure 28 In this embodiment, compared to the scenario where the feed ports of the two antennas switch operation (i.e., antenna switching), the gain of antenna 1 and antenna 2 provided in this application is improved over most areas. For example, in the scenario of achieving the same coverage area, the gain of the switching antenna at 60% coverage area is -2dBic, while the gain of antenna 1 and antenna 2 provided in this application at 60% coverage area is -1dBic, an improvement of more than 1dB. For example, in the scenario of achieving the same gain, the switching antenna at -1dBic only achieves 4% coverage, while antenna 1 and antenna 2 provided in this application can achieve 60% coverage at -1dBic. For example, when the coverage is set to 80%, the gain of the switching antenna is only -2.7dBic, while the gain of antenna 1 and antenna 2 proposed in this application is -2dBic. Therefore, compared to the switching operation mechanism, the gain of antenna 1 and antenna 2 implemented by the phase modulation mechanism provided in this application is improved by more than 0.7dB in the 80% coverage area.

[0196] exist Figure 28 Compared to a single CM excitation (i.e., a common-mode antenna), the coverage of antennas 1 and 2 proposed in this application embodiment is significantly improved at the same gain, and the gain can also be improved while maintaining a certain coverage.

[0197] The antennas 1 and 2 provided in this application embodiment achieve excellent beam coverage by adjusting the phase difference between the two feed ports, reaching 80% coverage in areas with a circular polarization gain above -2dBic. The spatial coverage of RHCP gain is basically similar for both antennas 1 and 2. The method of slotting in the metal floor provided in this application embodiment can improve spatial coverage. Furthermore, this application embodiment does not limit the antenna type, as long as it can excite different current modes on the same metal floor under dual feed port excitation with different phase differences. It also further illustrates that beam steering can be achieved by adjusting the phase difference, thereby providing effective and stable satellite communication.

[0198] This application does not limit the antenna configuration for the dual-feed port phase modulation mechanism. The aforementioned method of slotting the short or long side of the metal ground plane excites different current modes in the metal ground plane, achieving beam steering and full-space coverage. In practice, this dual-feed port phase modulation method can also be applied to other antenna types. For example, the feed ports of two inverted-F structure (IFA antenna) can also excite orthogonal current modes in the metal ground plane.

[0199] In some embodiments, such as Figure 29 As shown, in antenna 3, the first excitation element is a first radiating stub 321 of an inverted F structure, and the second excitation element is a second radiating stub 421 of an inverted F structure. The first short-circuit point 3211 of the first radiating stub 321 is connected to the first connection point 21 of the metal ground 20, and the first connection point 21 is the point on the metal ground 20 closest to the first short-circuit point 3211. The second short-circuit point 4211 of the second radiating stub 421 is connected to the second connection point 22 of the metal ground 20, and the second connection point 22 is the point on the metal ground 20 closest to the second short-circuit point 4211.

[0200] The above Figure 29 The following description uses a coaxial cable as an example, with the first feeder assembly (1st feeder assembly 50) or the second feeder assembly 60 being axially symmetrical about the first radiating stub 321 and the second radiating stub 421. The inner conductor of the first feeder assembly 50 is connected to the first feed point 311 of the first radiating stub 321, and the outer conductor of the first feeder assembly 50 is connected to the metal ground plane 20, forming the first feed port. Similarly, the inner conductor of the second feeder assembly 60 is connected to the second feed point 411 of the first radiating stub 321, and the outer conductor of the second feeder assembly 60 is connected to the metal ground plane 20, forming the second feed port.

[0201] like Figure 29 As shown, Figure 29 This is a schematic diagram of the antenna 3 provided in the embodiments of this application. Figure 1 . Figure 29Figure A shows a top view of antenna 3, which is located on an idealized plane. Antenna 3 includes two short-circuit points and two feed ports. Figure 29 Figure B in the middle and Figure 29 Figure C in the diagram shows enlarged views of the two IFA antennas. Figure 29 Figure D in the diagram shows a partial magnified view of the antenna to show the dielectric substrate 10.

[0202] The structure of an IFA antenna can be seen as an evolution of a quarter-wavelength monopole antenna. By bending the monopole antenna by 90°, an inverted L-shaped antenna is obtained. An inverted L-shaped short-circuit stub is added at the corner of the inverted L-shaped antenna, and this stub is connected to a metal ground plane to form the IFA antenna. The IFA antenna consists of a transmission line with an open-circuit termination and a transmission line with a short-circuit termination connected in parallel. The open-circuit transmission line acts as a load at resonance, while the short-circuit transmission line acts as an inductor in series at resonance.

[0203] The above Figure 29 The length of the IFA antenna shown refers to the length of the open-circuit transmission line, that is, the distance from the feed point to the open-circuit termination point. The length of the IFA antenna is slightly greater than one-quarter of the wavelength of 1.5 GHz on the dielectric substrate. Specific values ​​can be adjusted according to simulation or actual measurement environments, and this application embodiment does not impose limitations on this. Figure 29 The impedance matching of the IFA antenna in the target frequency band can be achieved by adjusting the length of the open-circuit transmission line and the short-circuit transmission line.

[0204] It should be noted that, Figure 29 The IFA antenna shown is located on the short side of the metal ground plane 20. The feed port of the IFA antenna can be located near the center of the short side of the metal ground plane 20, as long as the endpoint of the extension direction of the IFA antenna does not exceed the metal ground plane. Of course, the IFA antenna can also be located on the long side of the metal ground plane 20. Figure 29 The two IFA antennas shown can be axially symmetrical on the metal ground plane 20. Of course, the two IFA antennas can also be centrally symmetrical on the metal ground plane 20. Figure 29 The short-circuit point of the IFA antenna shown can be directly soldered to the metal ground plane 20 of the dielectric substrate 10, or it can be soldered to a metal sheet with through holes on the top surface of the dielectric substrate 10. Figure 29The diagram also shows the feed port of the IFA antenna. The inner conductor of the coaxial cable is connected to the feed port of the IFA antenna. The outer conductor of the coaxial cable can be soldered on the metal ground plane 20 of the dielectric substrate 10, or it can be soldered to a metal sheet with through holes on the top surface of the dielectric substrate 10. This application embodiment does not limit the position of the IFA antenna on the metal ground plane 20, the soldering method of the IFA antenna's short-circuit point, or the soldering method of the coaxial cable, as long as current can be excited on the metal ground plane 20. Further details are omitted here.

[0205] Figure 29 While it may be an ideal antenna, in practical applications, a metal frame for the terminal device is also required. Figure 29 ,like Figure 30 As shown, Figure 30 This is a schematic diagram of the antenna 3 provided in the embodiments of this application. Figure 2 , Figure 30 Figure A in the diagram shows a top view of the IFA antenna after the metal frame has been added. Figure 30 Figure B in the diagram shows a 3D view of the IFA antenna after the addition of the metal frame. Figure 30 It can be seen that the radiating stubs of the two IFA antennas can be part of the metal frame. Optimizing the antenna design within the limited space of the terminal device, while minimizing changes to the existing structure, reduces the complexity of the antenna design and increases the feasibility of antenna implementation.

[0206] right Figure 29 The antenna 3 shown in the figure is simulated, taking a target frequency band center frequency of 1.5GHz as an example. Figure 31 As shown, Figure 31 This is a schematic diagram of the current distribution of antenna 3 provided in the embodiments of this application. Figure 31 This is the current distribution diagram of antenna 3 at a frequency of 1.5 GHz, shown in vector form Jsurf (A / m). Figure 31 Figure A shows the current distribution of antenna 3 under common-mode (CM) excitation, where common-mode refers to a phase difference of 0° between the two IFA antennas. According to... Figure 31 The current distribution in diagram A is as follows: Figure 32 Figure A in the diagram shows the radiation pattern corresponding to the CM excitation.

[0207] Figure 31 Figure B in the diagram shows the current distribution of antenna 3 under differential mode (DM) excitation, where differential mode refers to a 180° phase difference between the two IFA antennas. According to... Figure 31 The current distribution in diagram B, as shown Figure 32 Figure B in the diagram shows the radiation pattern corresponding to the CM excitation.

[0208] In this embodiment, the metal ground plane of the terminal device is utilized. By adjusting the phase difference between the two feed ports, the orthogonal mode of the metal ground plane can be excited, as described above. Figure 31 and Figure 32 As shown, this eliminates the inherent radiation null point of traditional array beam steering. This antenna features a wide beam and high coverage, making it suitable for low-Earth orbit satellite communications.

[0209] Depend on Figure 31 and Figure 32 It can be seen that the current in the metal ground plane varies under different excitations, resulting in different radiation patterns. For both common-mode and differential-mode orthogonal excitations, the current distribution in the metal ground plane is orthogonal. However, because the metal ground plane and the IFA antenna lack left-right symmetry, the spatial coverage of the IFA antenna is slightly lower than that of the slotted antenna, but it still achieves the technical effect of beam steering to achieve full spatial coverage.

[0210] The antenna provided in this application embodiment achieves low gain and full-space coverage by adjusting the phase difference between the two feed ports. Essentially, this scheme uses two feed ports sharing a common metal ground plane as the radiator. Therefore, the first and second excitation elements in the antenna can be connected to form a third radiating stub 70. The antenna configuration can be as follows... Figure 33 As shown, Figure 33 This is a schematic diagram of antenna 4 provided in an embodiment of this application. Figure 33 Taking the third radiating stub 70 of the middle ring as an example, with the first and second sides being the same side, the following explanation is provided. The inner conductor of the first feed component is connected to the first feed point of the third radiating stub, and the outer conductor of the first feed component is connected to the metal ground plane, forming the first feed port. The inner conductor of the second feed component is connected to the second feed point of the third radiating stub, and the outer conductor of the second feed component is connected to the metal ground plane, forming the second feed port.

[0211] The above Figure 33 The antenna 4 shown includes a ring-shaped radiating stub, the length of which is related to the target frequency band and is slightly longer than half the wavelength of the center frequency of the target frequency band on the dielectric substrate. The two feed ports of antenna 4 are located on top of the metal ground plane 20, increasing the versatility of the antenna configuration. In practical applications, the third radiating stub can be located outside the terminal device, allowing for greater flexibility in its placement and structure.

[0212] It should be noted that, Figure 33The annular radiating stub shown is located on the short side of the metal floor 20. The two ends of the annular radiating stub are feed ports (i.e., the first feed port and the second feed port). The annular radiating stub has a symmetrical structure along the short side. Of course, the annular radiating stub can also be located on the long side of the metal floor 20, with both feed ports also located on the long side. Alternatively, the annular radiating stub can be located at any vertex of the metal floor 20, with one feed port located on the long side and the other on the short side. This embodiment does not limit the scope of this application.

[0213] The inner conductors of the two coaxial cables are connected one-to-one with the two feed ports of the annular radiating stub. The outer conductor of each coaxial cable can be soldered on the metal ground plane 20 of the dielectric substrate, or it can be soldered to a metal sheet with through holes on the top surface of the dielectric substrate. Figure 33 The same radiating stub shown is a ring radiating stub, but it can also be other structures, such as a broken line structure, an arc structure, an irregular structure, etc. This application does not limit the position of the ring radiating stub on the metal floor or the welding method of the coaxial cable, as long as current can be excited on the metal floor. See the description of the slotted antenna above; it will not be repeated here.

[0214] The phase modulation mechanism with dual-fed ports and a common-metal ground plane proposed in this application embodiment does not limit the form of the antenna; it can be as follows: Figures 5-10 as well as Figure 25 The slotted antenna shown can also be as follows: Figure 29 and Figure 30 The two frame IFA antennas shown can also be as follows: Figure 33 Other forms shown, as long as the antenna achieves improved spatial coverage through dual-feed ports and a common metal ground plane, are all within the protection scope of the embodiments of this application.

[0215] In practical applications, the above Figures 5-25 The slotted design shown is located inside the terminal device, as described above. Figure 29 and Figure 30 The IFA antenna shown is located inside the terminal device and does not affect the external structure of the terminal device. The third radiating stub can be located outside the terminal device. The placement and structure of the third radiating stub are more flexible and diverse.

[0216] This application provides a terminal device that includes an antenna (e.g., antenna 1, antenna 2, antenna 3, or antenna 4) as shown in any of the above embodiments; the terminal device communicates with a low-Earth orbit satellite system through the antenna.

[0217] For example, the above Figures 5-33This paper describes the antenna structure using a mobile phone as an example, with the phone's metal ground plane measuring 140mm × 70mm. The mobile phone communicates with a low-Earth orbit (LEO) satellite system through this antenna. This technical architecture can be adapted to other electronic devices. In other words, the dual-feed port and shared metal ground plane phase modulation mechanism provided in this embodiment can also be used in other electronic devices to achieve direct LEO satellite communication. Other electronic devices can include foldable mobile phones, tablets, wearable devices, in-vehicle devices, laptops, etc.

[0218] In some embodiments, the terminal device has a foldable structure; the metal ground plane in the antenna has a foldable structure; or, the terminal device includes two independent metal ground planes, and the metal ground plane in the antenna is either an independent metal ground plane.

[0219] For example, taking a foldable phone as an example, if the metal ground plane of the antenna in the foldable phone is a foldable structure with dimensions of 140mm × 70mm, the antenna design scheme described above can be reused. If the foldable phone includes two independent metal ground planes, the two excitation elements of the antenna can be placed in either metal ground plane; that is, the metal ground plane in the antenna can be any independent metal ground plane. The antenna structure can then be fine-tuned according to the dimensions of the metal ground plane to achieve the technical effect of exciting orthogonal mode currents on the metal ground plane within the target frequency band, thus achieving full-space coverage.

[0220] When applying the antennas provided in this application to electronic devices of other sizes, the dimensions and dielectric constant of the substrate of the electronic device also need to be further considered. For slotted antennas, the length of the slots and the size of the matching patch (i.e., the area of ​​the matching patch facing the metal ground plane) are finely adjusted by combining the dimensions and dielectric constant of the substrate to achieve impedance matching in the target frequency band. For IFA antennas, the lengths of the radiating stubs and short-circuit stubs are finely adjusted by combining the dimensions and dielectric constant of the substrate to achieve impedance matching in the target frequency band. For ring radiating stubs, the length of the ring radiating stubs is finely adjusted by combining the dimensions and dielectric constant of the substrate. This application will not elaborate on these details, as long as orthogonal mode currents can be excited on the metal ground plane within the target frequency band to achieve full-space coverage.

[0221] Based on the terminal device provided in any of the above embodiments, this application also provides a communication method, such as... Figure 34 As shown, Figure 34 This is an exemplary flowchart illustrating a communication method provided in an embodiment of this application. The method can be executed by a terminal device; it can also be executed by a cloud server, with the cloud server connected to the terminal device and interacting with it for data exchange. The method includes:

[0222] S201. Based on multiple preset phase differences, current is supplied to the first and second feeding components of the antenna of the terminal device, respectively, and the signal strength corresponding to each of the multiple preset phase differences is obtained when the terminal device communicates with the low-orbit satellite system.

[0223] S202. Based on the phase difference corresponding to the maximum value among multiple signal strengths, current is supplied to the first and second feeding components of the antenna respectively, so that the radiation intensity of the antenna is maximized.

[0224] In this embodiment of the application, without knowing the location of the low-orbit satellite, based on the above... Figures 14-16 Multiple phase differences are provided. These phase differences are iterated through, and the signal strength corresponding to each phase difference during communication between the terminal device and the low-Earth orbit satellite system is obtained. The phase difference with the highest signal strength is selected. During communication, current is supplied to the two feed ports of the antenna according to this phase difference, maximizing the antenna's radiation intensity.

[0225] When supplying currents with a phase difference to two feed ports, current excitation with different phase differences can be achieved by a phase shifter.

[0226] This communication method places no restrictions on the user's terminal device posture, reducing the location requirements for satellite communication and improving its efficiency. Furthermore, because wide-beam antennas offer comprehensive coverage, even if the low-Earth orbit (LEO) satellite moves, the communication quality between the LEO satellite and the antenna will not be significantly affected, thus improving the stability of satellite communication.

[0227] Based on the terminal device provided in any of the above embodiments, this application also provides a communication method, such as... Figure 35 As shown, Figure 35 This is an exemplary flowchart illustrating another communication method provided in this application. The method can be executed by a terminal device; it can also be executed by a cloud server, with the cloud server connected to the terminal device and interacting with it for data exchange. The method includes:

[0228] S301. Obtain the positional relationship between the low-Earth orbit satellite system and the terminal equipment, and the polarization mode of the low-Earth orbit satellite system.

[0229] S302. Determine the target phase difference based on the phase distribution diagram corresponding to the spatial radiation gain of the antenna of the terminal equipment, the positional relationship, polarization mode, and the spatial radiation gain of the antenna. The phase distribution diagram indicates the phase difference corresponding to the maximum gain of each spatial point under different polarization modes.

[0230] In this embodiment, the phase distribution map includes a phase distribution map corresponding to left-hand circular polarization and a phase distribution map corresponding to right-hand circular polarization. The phase distribution map corresponding to left-hand circular polarization indicates the phase difference at which each spatial point reaches maximum gain under left-hand circular polarization, while the phase distribution map corresponding to right-hand circular polarization indicates the phase difference at which each spatial point reaches maximum gain under right-hand circular polarization. Based on the polarization mode of the low-Earth orbit satellite system, a phase distribution map consistent with that polarization mode is selected. For example, if the low-Earth orbit satellite system is right-hand circularly polarized, then the phase distribution map corresponding to right-hand circular polarization is selected.

[0231] A spatial coordinate system is constructed with the terminal device as the origin. The position of the low-Earth orbit satellite system is mapped onto this spatial coordinate system to obtain the positional relationship between the two. The positional relationship can include θ and φ. After the low-Earth orbit satellite system moves, the positional relationship between the two is re-determined using the above method. Based on θ and φ, the phase difference corresponding to the point (θ, φ) is found on the phase distribution map and used as the target phase difference.

[0232] S303. Based on the target phase difference, current is supplied to the first and second feeding components of the antenna respectively, so that the radiation intensity of the antenna is maximized at the position facing the low-orbit satellite system.

[0233] In this embodiment, knowing the relative positions of the low-Earth orbit satellite and the terminal device (for example, the terminal device can be a fixed device placed in a certain location), the positional relationship between the low-Earth orbit satellite and the terminal device can be determined based on the position of the low-Earth orbit satellite. Based on the above... Figure 16 The phase distribution diagram is shown. A suitable phase difference can be directly selected from the phase distribution diagram based on the positional relationships. During communication, current is supplied to the two feed ports of the antenna according to this phase difference, maximizing the radiation intensity of the antenna towards the low-Earth orbit satellite system.

[0234] When supplying currents with a phase difference to two feed ports, the current excitation of the target phase difference can be achieved by a phase shifter.

[0235] It should be noted that the above Figure 16 The polarization pattern shown is a right-handed phase distribution diagram. If the polarization pattern of a low-Earth orbit satellite system is also right-handed, the above-mentioned... Figure 16The provided phase distribution map determines the phase difference corresponding to the antenna reaching maximum gain. Similarly, embodiments of this application can also provide a phase distribution map with left-handed polarization. As mentioned above, the maximum value of the eight LHCP gain values ​​corresponding to each spatial point (θ, φ) is extracted to obtain the combined LHCP gain pattern. Furthermore, the phase difference corresponding to each spatial point (θ, φ) reaching maximum LHCP gain can be statistically analyzed to obtain the phase distribution map. If the polarization of the low-Earth orbit satellite system is left-handed, the left-handed phase distribution map can be used to determine the phase difference corresponding to the antenna reaching maximum gain. Embodiments of this application do not impose limitations on this.

[0236] This communication method is applicable to situations where the positional relationship between a low-Earth orbit satellite system and a terminal device is relatively fixed. It can directly filter out suitable phase differences, thereby improving the efficiency of satellite communication.

[0237] The foregoing has provided a detailed example of the antenna provided in this application. It is understood that the corresponding terminal device, in order to implement the above functions, includes the hardware structure necessary to perform each function.

[0238] In the embodiments provided in this application, it should be understood that the disclosed structures can be implemented in other ways. For example, the structural embodiments described above are merely illustrative. For instance, the division of modules or units is only a logical functional division, and in actual implementation, there may be other division methods. For example, multiple units or components may be combined or integrated into another device, or some features may be ignored or not executed. Furthermore, the coupling or direct coupling or communication connection shown or discussed may be through some interfaces, or indirect coupling or communication connection of devices or units, and may be electrical, mechanical, or other forms.

[0239] The units described as separate components may or may not be physically separate. A component shown as a unit can be one or more physical units; that is, it can be located in one place or distributed in multiple different locations. Some or all of the units can be selected to achieve the purpose of this embodiment according to actual needs.

[0240] The above description is merely a specific embodiment of this application, but the scope of protection of this application is not limited thereto. Any variations or substitutions that can be easily conceived by those skilled in the art within the scope of the technology disclosed in this application should be included within the scope of protection of this application. Therefore, the scope of protection of this application should be determined by the scope of the claims.

Claims

1. An antenna, characterized in that, The antenna is used to communicate with a low-Earth orbit satellite system, and the antenna includes: a dielectric substrate, a metal ground plane, a first excitation element, a second excitation element, a first feeding assembly, and a second feeding assembly; The metal floor is attached to the first surface of the dielectric substrate; The first excitation element is disposed on a first side of the metal floor, and the second excitation element is disposed on a second side of the metal floor; the dimensions of the first excitation element and the second excitation element are related to the target frequency band; The inner conductor of the first feeding component is connected to the first feeding point of the first excitation element, and the outer conductor of the first feeding component is connected to the metal ground plane. The inner conductor of the second feeding component is connected to the second feeding point of the second excitation element, and the outer conductor of the second feeding component is connected to the metal ground plane; The first power supply component is used to provide a first excitation current to the first excitation element; The second feeding component is used to provide a second excitation current to the second excitation element; The metal floor is used to achieve spatial directional coverage of the target frequency band by radiating beam steering under the action of the first excitation current and the second excitation current with different phase differences.

2. The antenna according to claim 1, characterized in that, The first current distribution and the second current distribution, which are orthogonal to each other on the metal ground, make the radiation null point of the antenna under common-mode excitation complementary to the radiation null point under differential-mode excitation. The first current distribution refers to the current distribution on the metal ground when the first excitation current and the second excitation current are common-mode, and the second current distribution refers to the currents on the metal ground that are orthogonal when the first excitation current and the second excitation current are differential-mode.

3. The antenna according to claim 1 or 2, characterized in that, The structures of the first excitation element and the second excitation element are axially or centrally symmetrical on the metal floor.

4. The antenna according to any one of claims 1-3, characterized in that, The metal floor has a rectangular structure; The first side and the second side are either the two long sides of the metal floor or the two short sides of the metal floor.

5. The antenna according to any one of claims 1-4, characterized in that, The outer conductor of the first power supply component is connected to a first region of the metal floor; the vertical distance between the first region and the first power supply point is less than a first distance threshold. The outer conductor of the second power supply component is connected to a second region of the metal floor; the vertical distance between the second region and the second power supply point is less than a second distance threshold.

6. The antenna according to claim 5, characterized in that, The first excitation element includes a first gap and a first matching plate, and the first feed point is disposed on the first matching plate. The second excitation element includes a second gap and a second matching plate, and the second feed point is disposed on the second matching plate. The first gap extends in a direction away from the first side; The first matching piece is disposed on the second surface of the dielectric substrate and near the first edge, for impedance matching of the first gap in the target frequency band; the projection of the first matching piece on the metal floor and the first area are respectively located on both sides of the first gap; The second gap extends in a direction away from the second side; The second matching piece is disposed on the second surface and close to the second side, and is used to match the impedance of the second gap in the target frequency band; the projection of the second matching piece on the metal floor and the second area are respectively located on both sides of the second gap.

7. The antenna according to claim 6, characterized in that, The first excitation element further includes a first grounding plate disposed on the second surface and close to the first side, the projection of the first grounding plate on the metal floor overlaps with the first area, and the first grounding plate is connected to the metal floor through a through hole; the outer conductor of the first power supply component is connected to the first grounding plate; And / or, The second excitation element further includes a second grounding plate disposed on the second surface and close to the second side, the projection of the second grounding plate on the metal floor overlaps with the second region, and the second grounding plate is connected to the metal floor through a through hole; the outer conductor of the second power supply component is connected to the second grounding plate.

8. The antenna according to claim 6 or 7, characterized in that, The first gap or the second gap can be any one of an L-shaped structure, a straight line structure, an arc structure, or a broken line structure.

9. The antenna according to any one of claims 6-8, characterized in that, The starting end of the first gap is located at the center of the first side, and the starting end of the second gap is located at the center of the second side; Alternatively, the starting end of the first gap is centrally symmetrical to the starting end of the second gap.

10. The antenna according to any one of claims 6-9, characterized in that, The projection of the first matching piece onto the metal floor overlaps with the first gap. And / or, the projection of the second matching piece onto the metal floor overlaps with the second gap.

11. The antenna according to any one of claims 6-10, characterized in that, In the target frequency band, the areas of the first and second matching plates facing the metal ground plane, as well as the lengths of the first and second gaps, are related to the size and dielectric constant of the dielectric substrate.

12. The antenna according to any one of claims 6-11, characterized in that, The dielectric substrate has a first groove that corresponds to the structure and position of the first gap. And / or, a second groove corresponding to the structure and position of the second gap is formed on the dielectric substrate.

13. The antenna according to any one of claims 1-5, characterized in that, The first excitation element is the first radial branch of the inverted F structure, and the second excitation element is the second radial branch of the inverted F structure; The first short-circuit point of the first radiating branch is connected to the first connection point of the metal floor, and the first connection point is the point on the metal floor closest to the first short-circuit point; The second short-circuit point of the second radiating branch is connected to the second connection point of the metal floor, which is the point on the metal floor closest to the second short-circuit point.

14. The antenna according to claim 1 or 2, characterized in that, The first excitation element and the second excitation element are connected to form a third radiating branch.

15. A terminal device, characterized in that, Includes the antenna as described in any one of claims 1-14; The terminal device communicates with the low-Earth orbit satellite system via the antenna.

16. The terminal device according to claim 15, characterized in that, The terminal device has a foldable structure; The metal ground plane in the antenna has a foldable structure; Alternatively, the terminal device may include two separate metal ground planes, and the metal ground plane in the antenna may be either of the separate metal ground planes.

17. A communication method, characterized in that, The method is applied to the terminal device according to claim 15 or 16; the method includes: According to multiple preset phase differences, current is provided to the first and second feeding components of the antenna of the terminal device, respectively, and the signal strength corresponding to each of the multiple preset phase differences is obtained when the terminal device communicates with the low-orbit satellite system. Based on the phase difference corresponding to the maximum value among the multiple signal strengths, current is supplied to the first feed component and the second feed component of the antenna respectively, so that the radiation intensity of the antenna is maximized.

18. A communication method, characterized in that, The method is applied to the terminal device according to claim 15 or 16; the method includes: Obtain the positional relationship between the low-Earth orbit satellite system and the terminal device, and the polarization mode of the low-Earth orbit satellite system; The target phase difference is determined based on the positional relationship, the polarization mode, and the phase distribution diagram corresponding to the spatial radiation gain of the antenna of the terminal device; the phase distribution diagram indicates the phase difference corresponding to the maximum gain of each spatial point under different polarization modes. According to the target phase difference, current is supplied to the first and second feed components of the antenna respectively, so that the radiation intensity of the antenna is maximized at the position facing the low-Earth orbit satellite system.

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