Method for controlling a Vienna rectifier

Abstract

The invention relates to a method for generating a current target value for a charging device connected to a power grid, the method comprising: a step of measuring (61) at least one voltage; a filtering step (62) during which a current target value is generated according to the measured voltage (V mes ) and the electrical angular frequency of the grid (ω G ) to calculate the filtered voltage (V ftr ); Based on the at least one measured voltage and the at least one filtered voltage (V ftr ) to estimate the frequency (f) of the measured voltage (63) G ) and amplitude (V G ) step; merging step (64), during which step, according to the measured voltage (V mes ) and the filtered voltage (V ftr ) to calculate the combined voltage (V cs ); and according to the combined voltage (V cs ) and the estimated amplitude (V G ) to generate (65) the current target value (i req ) steps.

Description

Technical Field

[0001] The present invention relates to a method for controlling a rectifier of a single-phase or three-phase input charging device comprising an isolated AC to DC converter, particularly suitable for use as an on-board device in an electric or hybrid motor vehicle. Background Art

[0002] These vehicles are equipped with high-voltage batteries and typically include an on-board charger (OBC), a battery charging device installed directly in the vehicle. The primary function of these chargers is to recharge the battery from the power available on the power distribution grid. Therefore, these chargers convert AC current into DC current. Desired standards for charging equipment, and more specifically OBCs, include high efficiency, small size, electrical isolation, good reliability, safe operation, low electromagnetic interference emissions, and low harmonic levels in the input current.

[0003] The purpose of the present invention is applicable to single-phase and three-phase charging equipment. By way of demonstration, Figure 1 The known topology of an isolated charging device 10 on board an electric or hybrid vehicle for recharging the vehicle's high-voltage battery from a three-phase power grid 30 is shown. The onboard charging device 10 is connected to the three-phase power grid via the grid's line impedance 40. This topology can be adapted for single-phase charging devices.

[0004] To implement AC-to-DC conversion with electrical isolation, it is known to use a charging device 10 that includes a first AC-to-DC converter with a power factor correction (PFC) circuit 20 to limit input current harmonics, and a second DC-to-DC converter (DC current to DC current) 12 for controlling charging and also providing isolation for safety. An input filter 13 is conventionally integrated at the input of the on-board charging device 10, upstream of the PFC circuit 20 relative to the three-phase power grid 30.

[0005] The PFC circuit 20 is controlled by an integrated controller (not shown) that analyzes and corrects the current-voltage trend in real time. From this, it derives shape errors by comparing it with the rectified sine wave of the voltage and corrects these shape errors by controlling the amount of energy that passes through the high-frequency chopping and stores it in the inductor. More precisely, its effect is to achieve a non-phase-shifted and largely sinusoidal current at the input of the charger's power supply.

[0006] For the PFC circuit 20, it is known in particular from the prior art document CN 104811061 to use a three-level three-phase rectifier with three switches, generally referred to as a three-phase Vienna rectifier, as in the prior art documents EP 94120245 and Figure 2 As described in .

[0007] Choosing this topology is particularly advantageous from a power factor correction performance perspective.

[0008] In the three-phase Vienna rectifier 20 , each phase of the three-phase AC input voltage 30 is connected to a switching leg 1 , 2 , 3 of the rectifier 20 , which is provided with a power switching unit Sa, Sb, Sc, respectively, through a corresponding inductor La, Lb, Lc.

[0009] Each of these power switching units Sa, Sb, Sc is positioned between the corresponding inductor La, Lb, Lc and a center tap O, which is located between the two output voltages V of the rectifier 20. DCH With V DCL The two output voltages correspond to the voltage on the first output capacitor C1 connected between the center tap O and the positive power supply line H, and the voltage on the second output capacitor C2 connected between the center tap O and the negative power supply line L, respectively.

[0010] Typically, to control such a Viennese rectifier 20, the voltage and current at the input of each switch Sa, Sb, Sc and the voltage and current at the output of the rectifier are measured, and a control loop is used to generate the duty cycle required to control the average on-time of these switches Sa, Sb, Sc.

[0011] However, one problem with this type of structure is that when the measured voltage is affected by harmonics or imbalance, optimal generation of the current target value cannot be ensured, and generation of the active power target value is unreliable.

[0012] The problem of imbalance of the measured voltage is known in particular from document CN 103187887 B, which describes a controller for a Viennese rectifier using sinusoidal target values, but does not disclose any solution to these problems.

[0013] US Pat. No. 8,971,068 B2 describes a device for suppressing various harmonics caused by a high-voltage three-phase unidirectional rectifier to meet or approach a predetermined threshold for the absolute value of the phase difference between the input voltage of the AC current and the input voltage of the phase current of the unidirectional rectifier. However, US Pat. No. 8,971,068 B2 does not describe any possibility of providing a specific instantaneous active power target value.

[0014] Similarly, other known documents such as CN 104811061 A, CN 103227575 A and KR 101250454 B1 describe rectifiers with reactive power compensation, but do not disclose current target values.

[0015] Document EP 2 461 469 A3 proposes a system capable of generating a DC current target value in a rotating reference frame. However, this system has the disadvantage of using an additional variable, such as the phase of the rotating reference frame, to control the rectifier to generate the output signal.

[0016] Therefore, the object of the present invention is to generate current target values ​​in order to provide active power target values ​​as a function of the voltage of a three-phase or single-phase grid in a manner that is sufficiently reliable to overcome unbalances or harmonics that interfere with the grid.

[0017] In particular, document FR 3 056 851 is known, which discloses a method for generating a filtered current target value in order to provide an active power target value as a function of the voltage of a three-phase network and which aims to overcome imbalances in the network.

[0018] However, this solution cannot be applied to single-phase chargers. Furthermore, this solution exhibits unsatisfactory performance at voltage zero crossings and cannot estimate the frequency and amplitude of the grid voltage, making the controller power and performance relatively imprecise.

[0019] Therefore, a method for generating a current target value is needed in order to solve the prior art problems outlined above. Summary of the Invention

[0020] A method for generating a current target value for a charging device connected to a power grid is proposed, the method comprising:

[0021] - a step of measuring at least one voltage;

[0022] - a filtering step in which at least one filtered voltage is calculated based on said at least one measured voltage and the value of the electrical angular frequency of the electrical network;

[0023] - a step of estimating the frequency and amplitude of said at least one measured voltage based on said at least one measured voltage and said at least one filtered voltage;

[0024] - a merging step in which a merged voltage is calculated based on the at least one measured voltage and the filtered voltage; and

[0025] - A step of generating a current target value based on said combined voltage and the estimated amplitude.

[0026] Thus, a current control of a Viennese rectifier can be achieved which can be adapted for both a three-phase grid or a single-phase grid, and more generally for any N-phase grid, and which ensures relatively correct control in a relatively fast and reliable manner even in the case of an unbalanced grid and the presence of harmonics.

[0027] Furthermore, the method makes it possible to provide relatively optimal control during voltage zero crossings.

[0028] Advantageously and without limitation, the method is implemented several times in succession, and the value of the electrical angular frequency of the filtering step is determined based on the frequency estimated in the previous implementation. Thus, the electrical angular frequency can be determined relatively efficiently by previously measuring the estimated frequency.

[0029] Advantageously and without limitation, the measuring step comprises: measuring the phase voltages of the three-phase power grid; and calculating these measured voltages in a two-phase reference frame. Thus, the complexity and required calculation time can be relatively easily reduced. For example, the calculation in the two-phase reference frame can include a Clarke transform or a Concordia transform.

[0030] Advantageously and without limitation, the method comprises:

[0031] - a step of extracting the positive sequence component of these filtered voltages;

[0032] The estimation step is also based on the extracted positive sequence component. Therefore, current control can be made more efficient and accurate.

[0033] Advantageously and without limitation, the merging step is also based on the value of an amplitude threshold, so that the merged value can be limited to prevent possible incorrect or undesirable values.

[0034] The present invention also relates to a device for controlling a charging device connected to a power grid to implement the method described above, the device comprising:

[0035] - means for measuring at least one voltage;

[0036] - means for filtering said at least one measured voltage based on the value of the electrical angular frequency of the electrical network;

[0037] - means for estimating the frequency and the amplitude of said at least one measured voltage based on said at least one measured voltage and said at least one filtered voltage;

[0038] - means for combining said at least one measured voltage based on said at least one measured voltage and said at least one filtered voltage; and

[0039] - means for generating a current target value based on said combined voltage and said estimated amplitude.

[0040] The invention also relates to an assembly for recharging a battery of an electrical energy storage device and intended to be connected to an electrical network, the assembly having a power factor correction circuit, a DC to DC converter, a battery of the electrical energy storage device and a control device according to the invention.

[0041] Advantageously and without limitation, the power factor correction circuit comprises a Vienna rectifier.

[0042] Advantageously and without limitation, the recharging assembly is connected to a three-phase or single-phase electrical network.

[0043] The invention also relates to a motor vehicle comprising a recharging assembly as described above. BRIEF DESCRIPTION OF THE DRAWINGS

[0044] Other characteristics and advantages of the invention will become apparent on reading the description given below of a particular embodiment of the invention given by way of indication and not limitation, with reference to the accompanying drawings, in which:

[0045] - Figure 1 Shows the implementation according to Figure 3 A voltage converter according to a method of an embodiment of the present invention is shown;

[0046] - Figure 2 A three-phase Vienna rectifier known in the prior art is shown;

[0047] - Figure 3 shows the steps of filtering the measured voltage according to the present invention;

[0048] - Figure 4 shows the step of estimating the frequency and amplitude of the measured voltage according to the present invention;

[0049] - Figure 5 shows the merging steps according to the present invention;

[0050] - Figure 6 A flow chart showing a method according to the present invention; and

[0051] - Figure 7 A flow chart showing a method according to a second embodiment of the present invention is shown. DETAILED DESCRIPTION

[0052] Figure 2 The structure of a three-phase Vienna rectifier 20 used in the present invention known in the prior art is shown.

[0053] The three-phase Viennese rectifier 2 comprises three parallel input connections, each coupled to a phase of the three-phase power supply grid 30 via a series inductor coil La, Lb, Lc and each connected to a pair of switches Sa, Sb, Sc forming a first switching leg, a second switching leg and a third switching leg of the three-phase Viennese rectifier.

[0054] Each pair of switches Sa, Sb, Sc includes the corresponding input current i a 、i b 、i c The embodiment of the present invention is a head-to-tail series assembly consisting of a first corresponding switch Sah, Sbh, Sch that is driven when the corresponding input current is positive and a second corresponding switch Sal, Sbl, Scl that is driven when the corresponding input current is negative. In other words, a single switch driven on the switch branch is used to chop the current. These switches are formed by semiconductor components with controlled closing and opening, such as SiC-MOS (abbreviation for silicon carbide-metal oxide semiconductor) transistors connected in anti-parallel with diodes. This type of semiconductor is suitable for very high chopping frequencies. Switches Sah, Sbh, Sch are also called high-side switches, and switches Sal, Sbl, Scl are also called low-side switches.

[0055] The three-phase Viennese rectifier 20 also includes three parallel branches 1, 2 and 3, each branch having two diodes Dah and Dal, Dbh and Dbl, and Dch and Dcl, which form a six-diode three-phase bridge for unidirectional energy transfer and rectifying the current and voltage obtained from the three-phase power supply grid 30.

[0056] Each input of the three-phase Viennese rectifier 20 is connected to a connection point between two diodes of the same branch 1 , 2 and 3 via a respective parallel input connection.

[0057] The two common ends of the branches 1 , 2 and 3 form the two output terminals H and L (positive H and negative L respectively) of the three-phase Viennese rectifier 20 , which are intended to be coupled to the DC-to-DC device 12 .

[0058] The switching arms Sa, Sb and Sc of each phase are also connected to the connection points a, b and c between the two diodes of the first branch 1, the second branch 2 and the third branch 3 and the output voltage V of the three-phase Vienna rectifier 20 respectively. DCH and V DCL These output voltages correspond to the voltage on the output capacitor C1 between the positive output terminal H and the center tap O of the three-phase rectifier, and the voltage on the output capacitor C2 between the center tap O and the negative output terminal L of the three-phase rectifier 20, respectively.

[0059] according to Figure 1 In the overall topology shown in FIG, the voltages on the output capacitors C1 and C2 are independently controlled by the DC-to-DC converter of the charging device connected at the output of the three-phase Viennese rectifier 20. In other words, the output voltage of the three-phase Viennese rectifier 20 is controlled by the DC-to-DC converter 12.

[0060] The three-phase Viennese rectifier 20 at the input of the power supply plugged into the charger 10 takes on the role of correcting the charger's power factor. This role prevents interference currents (harmonics) generated by the charger from flowing through the impedance of the grid located upstream of the Viennese rectifier 20.

[0061] The switching arms Sa, Sb and Sc of each phase of the three-phase grid 30 are controlled by six PWM (Pulse Width Modulation) control signals with variable duty cycle and fixed chopping frequency equal to 140 kHz, these control signals being individually controlled, for example, by FPGA processing means (not shown) for high sampling frequency.

[0062] The processing means are therefore adapted to determine a duty cycle of the signal to control switching of the switches of the switching arms of the rectifier, which is required to control the sinusoidal current at the input of the rectifier.

[0063] The processing device implements a control method suitable for controlling the Vienna rectifier.

[0064] The control method according to the invention comprises the steps of measuring 61 the phase voltage of the power grid, filtering 62 the measured voltage, estimating 63 the frequency f of the current of the power grid. G and amplitude V G The steps of: a step of combining 64 the measured voltages; and a step of generating 65 a current target value.

[0065] In a first embodiment of the invention comprising a three-phase charging device, the phase voltage v of each electrical phase is measured. a mes 、v b mes 、v c mes .

[0066] A step of filtering 62 the measured voltage is then carried out.

[0067] The purpose of filtering is to extract the frequency components of the noise signal. Figure 3 The presented filter is based on the measured voltage components transformed into the Clarke domain, the electrical angular frequency ω of the grid voltage G (corresponding to 2πf G , where f G is the frequency of the grid voltage) and is implemented according to Figure 3 According to the logic layout proposed in , the filter includes an adjustment gain K1, two multipliers x, two integrators 1 / s, and two adders.

[0068] according to Figure 3 The filter has the advantage of being relatively simple to implement and having relatively low computational complexity. It offers a relatively good compromise between speed and filtering accuracy. For example, if a 50 Hz frequency is to be filtered, the filter provides a response time of less than 100 ms and very good accuracy in steady-state operation.

[0069] Furthermore, such a filter makes it possible to generate a signal which is orthogonal to the input signal (phase shift of +90°), which is particularly suitable for the method according to the invention, in particular for implementing steps such as:

[0070] - estimating 63 the frequency and amplitude of the input signal,

[0071] - estimating the reverse sequence component of the voltage in the three-phase case 621; and

[0072] - A method for controlling a charger via a single-phase power grid according to a second embodiment.

[0073] However, the present invention is not limited to this filtering, and any other suitable filtering may be used.

[0074] In order to apply the filter to a three-phase grid, first measure the three-phase voltage v for each phase. a mes 、v b mes 、v c mes , or according to an alternative, the three-phase phase voltages are calculated based on the measured values ​​of the phase-to-phase three-phase voltages.

[0075] Next, the components α and β of the voltage are calculated 611 by applying the Clarke transform (three phase to two phase).

[0076] The Clarke transformation allows calculations performed on the measured voltages to be converted from three dimensions (e.g., phase voltages Va, Vb, and Vc) into two dimensions in the reference frames α, β. Therefore, in the remainder of this embodiment, any reference to, in particular, measured and filtered voltages for a three-phase power grid should be understood as being considered in the reference frames α, β.

[0077] The filter is then applied to each voltage component vα, vβ to generate a filtered voltage and From these filtered voltages their corresponding quadrature components are derived and

[0078] However, if the grid is unbalanced, the quadrature component of α is not always aligned with β. In the case of a balanced grid, these quantities match. In other words, the consistency of the reference frames α and β depends on the balance between the measured phases, which is a well-known criterion of the Clarke transform.

[0079] Therefore, the estimation of the quadrature component is used to separate the imbalance (negative sequence component) from the main signal (positive sequence component).

[0080] In order to separate the unbalance from the main signal, a step of extracting 621 positive sequence components and negative sequence components from the three-phase voltage is implemented.

[0081] Specifically, it is known that the unbalanced three-phase voltage can be regarded as the sum of the following three components:

[0082] - Positive sequence component: balanced three-phase voltage with the same sequence as the original voltage;

[0083] - Reverse sequence component: balanced three-phase voltage in reverse sequence with the original voltage; and

[0084] -Zero-sequence component: A balanced three-phase voltage with 3 in-phase components (zero sequence, no phase shift between the 3 phases).

[0085] The components α, β of the positive sequence component of the filtered voltage are calculated using the following system of equations:

[0086]

[0087] The subscript p corresponds to the positive sequence component (positive sequence).

[0088] The components α, β of the reverse sequence component of the filtered voltage are calculated using the following system of equations:

[0089]

[0090] The subscript n indicates that this is a reverse sequence component (negative sequence).

[0091] Then, the inverse Clarke transform is applied to calculate the positive sequence three-phase voltage ( and ) and reverse order ( and )Three-phase voltage.

[0092] The calculation result of the zero-sequence component corresponds to 1 / 3 of the sum of the three-phase voltages.

[0093] An estimation 63 of the frequency f is then performed based on the voltage measured in the reference frame β, the filtered voltage and the voltage in quadrature with the filtered voltage. G and amplitude V Gsteps.

[0094] Apply the following equation to calculate the frequency:

[0095]

[0096] The amplitude of the fundamental component V G equal:

[0097]

[0098] Compared with a conventional structure using a phase-locked loop (PLL), the advantage is lower computational complexity.

[0099] Then, a merging step 64 is implemented, which consists in combining the measured voltage v of the phase in question based on the measured voltage v abc mes and the filtered voltage v abcp ftr Calculate the combined voltage v from the measured voltages abc cs ,like Figure 5 shown.

[0100] The purpose is to provide such a combined voltage v abc cs : close to the measured voltage v at low voltage abc mes , ensuring the best performance when the voltage crosses zero and getting closer to the filtered voltage as it moves further away from zero. This is achieved by using the following equation:

[0101] v abc cs =αv abcp ftr +(1-α)v abc mes

[0102] in,

[0103]

[0104] Vth is the threshold value of the magnitude of the measured voltage.

[0105] Vth_max is the maximum threshold, when it exceeds the threshold, only the filtered voltage v is used. abc ftr .

[0106] Vth_min is the minimum threshold below which only the measured voltage v is used. abc mes These thresholds can be adjusted and adapted by those skilled in the art based on the implemented charging device.

[0107] Between these two thresholds, a linear combination of the filtered voltage and the measured voltage is performed to ensure signal continuity and thus a smooth representation.

[0108] The original three-phase voltage in each phase is combined and (measured or calculated based on the measured phase-to-phase voltage) and its corresponding phase (positive sequence component) in the phase voltage and (calculated based on the filtered voltage respectively) are executed between.

[0109] Then, the step of generating 65 a current target value is performed.

[0110] For current control, the current target value i for each phase is calculated using the following equation: abc req :

[0111]

[0112] Among them I G is the peak value of the charging current, which is determined by the power P req (the power to be transferred by the phase in question) and the (estimated) grid voltage V G The magnitude is calculated and the value At saturation:

[0113]

[0114] A rate limiter is also applied to the power target value.

[0115] According to a second embodiment of the single-phase charging device of the present invention, Figure 7 The method first includes measuring the single-phase voltage V mes steps.

[0116] Next, use the Figure 3 The filtering step 72 is implemented by directly applying the measured single-phase voltage V mes .

[0117] refer to Figure 4 , then based on the measured voltage V mes and the filtered voltage V ftr To determine the frequency and amplitude of the 73 grid voltage.

[0118] Apply the following equation to calculate the frequency f G :

[0119]

[0120] Where k2 is the adjustment gain for the dynamic estimation range of frequency; the dynamic range varies in proportion to the gain k2.

[0121] The angular frequency of the signal ω G corresponds to:

[0122] ω G =2πf G

[0123] In addition, the fundamental component voltage V is calculated by the following equation: G :

[0124]

[0125] Figure 4 is a logical description of these calculations, where 1 / s is the integrator; k2 is outside the integrator, and 1 / 2π is also outside the integrator for calculating the frequency; and the signal at the input of k2 corresponds to the measured voltage signal V mes and the filtered voltage signal V ftr The product of these two.

[0126] Next, the steps of combining 74 and calculating a charging current target value 75 are performed in the same manner as in the first embodiment, except that the calculation is performed only for a single phase of the single-phase grid.

[0127] In other words, in single-phase form, the voltage V mes and the filtered voltage V ftr Execute between.

[0128] An alternative embodiment of the method according to the invention implements the step of estimating the harmonics of the measured voltage, which embodiment can also be applied to the first and second embodiments described below.

[0129] Therefore, according to this alternative, the number of filters implemented in order to extract harmonics of certain given orders is increased.

[0130] This can be done by Figure 3 The number of filters implemented is multiplied by n; n is the number of harmonics to be estimated / extracted. Then, for each filter x, the measured raw voltage v mes , multiply the angular frequency ω by the order h of the harmonic to be estimated / extracted (h×ω, to extract the h-order harmonic), and subtract the output of the other filter used from this voltage. In other words, the input of filter x corresponds to:

[0131]

[0132] where i=1 corresponds to the fundamental component (usually 50Hz or 60Hz), and

[0133] is the output of the filter of order i (i encompasses all other filters except the filter x in question), which corresponds to the output according to Figure 3 The output of the filter will be ω G Replace with i×ω G , and from the input v mes The result of the calculation performed on all harmonics (except i) is subtracted from .

[0134] In other words, in this alternative embodiment, one filter is used for the fundamental wave, and h similar filters are used in parallel. For these filters, the angular frequency ω is set to G multiplied by the harmonic order h. Therefore, the input of each filter Equal to the measured voltage v mes Subtract the results of the previous calculation steps of other filters For example, for a filter with harmonic x, from the measured voltage v mes Subtract the output calculated in the previous step where i covers all harmonics except harmonic x, ie except the output of the filter itself: i=1, i≠x up to i=h+1.

[0135] In this case, the output of each filter corresponds to an estimate of the harmonic of order h, and the estimate of the fundamental component is more accurate.This alternative embodiment does not change the other steps of the embodiment described, whether it is a single-phase or three-phase version.

Claims

1. A method for generating a current target value of a charging device connected to a power grid, the method comprising: - a measuring step of measuring (61, 71) at least one voltage; - a filtering step (62, 72) in which, based on at least one measured voltage (V mes ) and the electrical angular frequency of the grid (ω G ) to calculate at least one filtered voltage (V ftr ); - based on the at least one measured voltage and the at least one filtered voltage (V ftr ) to estimate (63, 73) the frequency (f G ) and amplitude (V G ) estimation step; - a merging step (64, 74) comprising: mes ) and the at least one filtered voltage (V ftr ) to calculate the combined voltage (V cs ), the calculation providing a combined voltage that approaches at least one low voltage measured voltage at low voltage and approaches at least one filtered voltage when further away from zero; as well as -Based on the combined voltage (V cs ) and the estimated amplitude (V G ) to generate the current target value (i req ) steps.

2. The method according to claim 1, characterized in that The method is implemented several times in succession, and the electrical angular frequency (ω G ) is based on the frequency (f G ) to determine.

3. The method according to claim 1 or 2, for a three-phase charging device, is characterized in that: The measuring step (61) comprises: measuring the phase voltage (v a mes , v b mes , v c mes ); and calculating (611) these measured voltages (v a mes , v b mes , v c mes ) steps.

4. The method according to claim 3, characterized in that The method includes: - Extract (621) the positive sequence components of these filtered voltages Steps; The estimation step (63) is also based on the extracted positive sequence component 5. The method according to claim 1 or 2, characterized in that: This merging step (64, 74) is also based on the values ​​of the amplitude thresholds (Vth, Vth_max, Vth_min).

6. A control device for controlling a charging device connected to a power grid to implement the method according to any one of claims 1 to 5, characterized in that: The control device includes: - means for measuring at least one voltage; - For the electrical angular frequency (ω) based on the power grid G ) value for at least one measured voltage (V mes ) means for filtering; - for determining a voltage based on the at least one measured voltage and the at least one filtered voltage (V ftr ) to estimate the frequency (f G ) and amplitude (V G ) - for determining, based on the at least one measured voltage (V mes ) and the at least one filtered voltage (V ftr ) to combine the at least one measured voltage, the means being capable of providing a combined voltage that approaches the at least one measured voltage at low voltages and approaches the at least one filtered voltage when further away from zero; and - for the combined voltage (V cs ) and the estimated amplitude (V G ) to generate the current target value (i req ) device.

7. A recharging assembly (10) for recharging a battery of an accumulator and intended to be connected to an electrical network, the recharging assembly having a power factor correction circuit (20), a DC to DC converter (12), a battery of the accumulator and a control device as claimed in claim 6.

8. The recharging assembly (10) according to claim 7, characterized in that The power factor correction circuit includes a Vienna rectifier.

9. A recharging assembly (10) according to claim 7 or 8, characterized in that The recharging assembly is connected to a three-phase or single-phase electrical network.

10. A motor vehicle comprising a recharging assembly as claimed in any one of claims 7 to 9.

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