A boost circuit, electronic device and control circuit

Abstract

Embodiments of the present application disclose a boost circuit, an electronic device and a control circuit. The boost circuit comprises a working circuit and a control circuit. The working circuit comprises a first resistor, an inductor, a capacitor, a load, a first switch and a second switch. The control circuit can generate a control signal to control the conduction state and conduction time of the first switch and the second switch, and further control the charge and discharge state and charge and discharge time of the inductor, so that the inductor is first in a discharge state and then in a charge state. When the current flowing through the inductor is disturbed, the valley point of the current flowing through the inductor can be adjusted by controlling the time when the inductor is in the discharge state, so that the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, and the fluctuation of the current flowing through the inductor due to the disturbance is eliminated.

Description

Technical Field

[0001] This application relates to the field of circuit technology, and more particularly to a boost circuit, an electronic device including the boost circuit, and a control circuit applied to the boost circuit. Background Technology

[0002] Boost converters, as a common power supply circuit, are frequently used in various circuit structures. However, with the gradual development of circuit technology, the application scenarios of boost converters are constantly changing. This requires boost converters to have good anti-surge capability to adapt to different application scenarios. Therefore, providing a boost converter with good anti-surge capability has become an urgent problem to be solved by those skilled in the art. Summary of the Invention

[0003] To address the aforementioned technical problems, this application provides a boost circuit that has good anti-fluctuation capability.

[0004] To address the above problems, the embodiments of this application provide the following technical solutions:

[0005] A boost circuit, the boost circuit comprising:

[0006] The working circuit includes a first resistor, an inductor, a capacitor, and a load. The first resistor and the inductor are connected in series. The first terminal of the first resistor is the input terminal of the boost circuit, receiving the supply voltage of the boost circuit. The second terminal of the first resistor is connected to the first terminal of the inductor, and the second terminal of the inductor is grounded through a first switch. The first terminal of the capacitor is connected to the second terminal of the inductor through a second switch, and the second terminal is grounded. The first terminal of the load is connected to the first terminal of the capacitor, and the second terminal is grounded. The voltage difference across the load is the output voltage of the boost circuit.

[0007] The control circuit has a first input terminal for the output voltage of the boost circuit, a second input terminal for the supply voltage of the boost circuit, and a third input terminal for the voltage difference across the first resistor. Based on the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor, the control circuit generates a control signal to control the conduction state and conduction time of the first switch and the second switch.

[0008] Optionally, the control circuit includes:

[0009] The calibration module receives the output voltage of the boost circuit at its input terminal and also includes a reference voltage. Based on the output voltage of the boost circuit and the reference voltage, the calibration module outputs a reference current.

[0010] The control module has the reference current input at its first input terminal, the output voltage of the boost circuit input at its second input terminal, the supply voltage input at its third input terminal, and the voltage difference across the first resistor input at its fourth input terminal. Based on the reference current, the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor, the control module outputs a duty cycle signal.

[0011] A pulse width modulation module is provided, wherein the duty cycle signal is input to the first input terminal of the pulse width modulation module, and the corresponding pulse signal is generated according to the duty cycle signal. The pulse signal is then output to the control terminal of the first switch and the control terminal of the second switch to control the conduction state and conduction time of the first switch and the second switch.

[0012] Optionally, the calibration module includes:

[0013] A calibration unit that obtains the difference between the output voltage of the boost circuit and the reference voltage based on the output voltage of the boost circuit and the reference voltage;

[0014] An adjustment unit adjusts the integral parameter of the calibration module based on the difference between the output voltage of the boost circuit and the reference voltage. When the difference between the output voltage of the boost circuit and the reference voltage is less than a first preset value, the current integral parameter of the calibration module is increased. When the difference between the output voltage of the boost circuit and the reference voltage is between the first preset value and a second preset value (including the endpoint value), the current integral parameter of the calibration module is decreased. When the difference between the output voltage of the boost circuit and the reference voltage is greater than the second preset value, the integral parameter of the calibration module is set to 0 until the difference between the output voltage of the boost circuit and the reference voltage is no greater than the second preset value. Then, the integral parameter of the calibration module is adjusted according to the relationship between the difference between the output voltage of the boost circuit and the reference voltage and the first preset value.

[0015] The calculation unit performs proportional, integral, and differential operations on the difference between the output voltage of the boost circuit and the reference voltage based on the integral parameters of the calibration module, and outputs the reference current.

[0016] Optional, also includes:

[0017] A first signal conversion module, wherein the input terminal of the first signal conversion module is connected to the first terminal of the load, and the output terminal is connected to the first input terminal of the control circuit;

[0018] The second signal conversion module has its input terminal connected to the input terminal of the boost circuit and its output terminal connected to the second input terminal of the control circuit.

[0019] The third signal conversion module has its input terminals connected to both ends of the first resistor, and its output terminal connected to the third input terminal of the control circuit.

[0020] Optionally, the operating circuit further includes:

[0021] The first voltage divider module includes a second resistor and a third resistor connected in series. The first terminal of the first voltage divider module is connected to the first terminal of the load, and the second terminal is grounded.

[0022] The second voltage divider module includes a fourth resistor and a fifth resistor connected in series. The first terminal of the second voltage divider module is connected to the input terminal of the boost circuit, and the second terminal is grounded.

[0023] Optionally, the control circuit further includes:

[0024] The noise shaping module receives the duty cycle signal at its input terminal, performs noise shaping on the duty cycle signal, and outputs the noise-shaped duty cycle signal to the pulse width modulation module.

[0025] Optional, also includes:

[0026] A level shifting module receives the pulse signal at its input terminal, converts the voltage of the pulse signal from a first voltage domain to a second voltage domain, and outputs the pulse signal converted from the first voltage domain to the second voltage domain to the control terminals of the first switch and the second switch, wherein the voltage in the second voltage domain is greater than the voltage in the first voltage domain.

[0027] Optionally, the control circuit further includes:

[0028] A current limiting module is provided, wherein the input terminal of the current limiting module is input to the current flowing through the inductor, and is used to limit the current flowing through the inductor.

[0029] Optionally, the control circuit further includes:

[0030] A mode monitoring module is provided, wherein the input terminal of the mode monitoring module receives the current flowing through the inductor, and is used to monitor the current flowing through the inductor and control the working mode of the inductor based on the current flowing through the inductor.

[0031] Optionally, when the mode monitoring module controls the operating mode of the inductor based on the current flowing through the inductor, it is specifically used for:

[0032] When the current flowing through the inductor is not greater than a third preset value, the inductor is controlled to be in intermittent working mode;

[0033] When the current flowing through the inductor is greater than the third preset value, the inductor is controlled to be in continuous working mode.

[0034] An electronic device comprising the boost circuit described in any of the above embodiments.

[0035] A control circuit is applied to a boost circuit, the boost circuit including a first resistor, an inductor, a capacitor, and a load. The first resistor and the inductor are connected in series, and the first terminal of the first resistor is the input terminal of the boost circuit, receiving the supply voltage; the second terminal of the first resistor is connected to the first terminal of the inductor, and the second terminal of the inductor is grounded through a first switch. The first terminal of the capacitor is connected to the second terminal of the inductor through a second switch, and the second terminal is grounded. The first terminal of the load is connected to the first terminal of the capacitor, and the second terminal is grounded. The voltage difference across the load is the output voltage of the boost circuit.

[0036] The control circuit receives the output voltage of the boost circuit at its first input terminal, the supply voltage of the boost circuit at its second input terminal, and the voltage difference across the first resistor of the boost circuit at its third input terminal. Based on the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor of the boost circuit, a control signal is generated to control the conduction state and conduction time of the first switch and the second switch of the boost circuit.

[0037] Optionally, the control circuit includes:

[0038] The calibration module receives the output voltage of the boost circuit at its input terminal and outputs a reference current based on the output voltage of the boost circuit and the reference voltage set in the calibration module.

[0039] The control module has the reference current input at its first input terminal, the output voltage of the boost circuit input at its second input terminal, the supply voltage of the boost circuit input at its third input terminal, and the voltage difference across the first resistor of the boost circuit input at its fourth input terminal. Based on the reference current, the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor of the boost circuit, the control module outputs a duty cycle signal.

[0040] A pulse width modulation module, wherein the duty cycle signal is input at the first input terminal of the pulse width modulation module, and the corresponding pulse signal is generated according to the duty cycle signal, and the pulse signal is output to the first switch and the second switch to control the conduction state and conduction time of the first switch and the second switch.

[0041] Optionally, it further includes: a noise shaping module, wherein the input terminal of the noise shaping module receives the duty cycle signal, is used to perform noise shaping on the duty cycle signal, and outputs the noise-shaped duty cycle signal to the pulse width modulation module.

[0042] Optionally, it further includes: a level shifting module, wherein the input terminal of the level shifting module receives the pulse signal, is used to convert the voltage of the pulse signal from a first voltage domain to a second voltage domain, and outputs the pulse signal converted from the first voltage domain to the second voltage domain to the control terminal of the first switch and the control terminal of the second switch, wherein the voltage in the second voltage domain is greater than the voltage in the first voltage domain.

[0043] Optionally, it may also include: a current limiting module, wherein the input terminal of the current limiting module receives the current flowing through the inductor and is used to limit the current flowing through the inductor.

[0044] Optionally, it also includes: a mode monitoring module, wherein the input terminal of the mode monitoring module is input to the current flowing through the inductor, for monitoring the current flowing through the inductor, and controlling the working mode of the inductor according to the current flowing through the inductor.

[0045] Compared with existing technologies, the above technical solution has the following advantages:

[0046] The boost circuit provided in this application embodiment includes a working circuit and a control circuit. The working circuit includes a first resistor and an inductor connected in series. The first terminal of the first resistor is the input terminal of the boost circuit, receiving the supply voltage, and the second terminal is connected to the first terminal of the inductor. The second terminal of the inductor is grounded through a first switch. A capacitor has its first terminal connected to the second terminal of the inductor through a second switch, and its second terminal is grounded. A load has its first terminal connected to the first terminal of the capacitor, and its second terminal grounded. The voltage difference across the load is the output voltage of the boost circuit. The control circuit receives the output voltage of the boost circuit at its first input terminal, the supply voltage at its second input terminal, and a third input terminal. The input terminal receives the voltage difference across the first resistor. Based on the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor, a control signal is generated to control the on and off states of the first and second switches. Thus, in each operating cycle of the boost circuit, the first switch is first turned off and the second switch is turned on, then the first switch is turned on and the second switch is turned off. In other words, in each operating cycle of the boost circuit, the inductor is first in a discharging state and then in a charging state, and the current flowing through the inductor first decreases and then increases.

[0047] Therefore, the boost circuit provided in this application embodiment, when the current flowing through the inductor is disturbed, that is, when there is a deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor in the current operating cycle, can determine the valley point of the current flowing through the inductor in the current operating cycle when the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, based on the deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor. In other words, it can obtain the valley value of the current flowing through the inductor in the current cycle and the time when the peak value of the current flowing through the inductor reaches the valley value when the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor. By determining the valley point of the current flowing through the inductor based on the deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor, the on and off states of the first and second switches, as well as the time spent in the off and on states, can be controlled by the control signal. This adjusts the charging and discharging state and the charging and discharging time of the inductor, thereby adjusting the valley point of the current flowing through the inductor. This ensures that the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, thus eliminating the fluctuations in the current flowing through the inductor caused by disturbances.

[0048] In addition, in the boost circuit provided in this application embodiment, after the output voltage of the boost circuit stabilizes, that is, when the boost circuit is working normally, the rate of decrease of the current flowing through the inductor is approximately the same in each working cycle of the boost circuit, and the rate of increase of the current flowing through the inductor is approximately the same. Therefore, when the peak point of the current flowing through the inductor is determined, the valley point of the current flowing through the inductor will also be determined. Furthermore, without changing the output voltage of the boost circuit and without considering the influence of external factors, the valley point of the current flowing through the inductor will not change in subsequent working cycles. Therefore, when there is a deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor, the valley point of the current flowing through the inductor is determined by the deviation between the peak value and the expected value of the current flowing through the inductor. After the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, the valley point of the current flowing through the inductor will not change in subsequent working cycles without changing the output voltage of the boost circuit and without considering the influence of external factors. This avoids subharmonic oscillations caused by fluctuations in the valley point of the current flowing through the inductor, giving the boost circuit better anti-fluctuation capability and thus better stability.

[0049] Therefore, the boost circuit provided in this application, when eliminating the fluctuations in the current flowing through the inductor caused by disturbances, not only ensures that the peak value of the current flowing through the inductor is the same as the expected value, but also avoids subharmonic oscillations, thus giving the boost circuit better anti-fluctuation capability. Attached Figure Description

[0050] To more clearly illustrate the technical solutions in the embodiments of this application or the prior art, the drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, the drawings described below are only some embodiments of this application. For those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0051] Figure 1 The waveform of the current flowing through the inductor in a boost circuit using trailing edge modulation is shown.

[0052] Figure 2 The waveform of the switching signal corresponding to the current waveform flowing through the inductor in the boost circuit using trailing edge modulation.

[0053] Figure 3 , Figures 5-8 , Figures 10-13 This is a schematic diagram of a boost circuit provided in an embodiment of this application;

[0054] Figure 4 A waveform diagram of the current flowing through the inductor in another boost circuit provided in an embodiment of this application;

[0055] Figure 9 A timing diagram of a boost circuit provided in an embodiment of this application;

[0056] Figure 14 This is a timing diagram of a boost circuit provided in an embodiment of this application. Detailed Implementation

[0057] The technical solutions of the embodiments of this application will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some embodiments of this application, and not all embodiments. Based on the embodiments of this application, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of this application.

[0058] Many specific details are set forth in the following description in order to provide a full understanding of this application. However, this application may also be implemented in other ways different from those described herein. Those skilled in the art can make similar extensions without departing from the spirit of this application. Therefore, this application is not limited to the specific embodiments disclosed below.

[0059] Secondly, this application provides a detailed description in conjunction with schematic diagrams. When detailing the embodiments of this application, for ease of explanation, the cross-sectional views illustrating the device structure may be partially enlarged, not adhering to the usual scale. Furthermore, the schematic diagrams are merely examples and should not limit the scope of protection of this application. In addition, actual fabrication should include three-dimensional spatial dimensions of length, width, and depth.

[0060] As described in the background section, providing a boost circuit with better resistance to fluctuations has become a problem that urgently needs to be solved by those skilled in the art.

[0061] The inventors discovered that existing boost circuits generally use trailing edge modulation, meaning that when the boost circuit is working, the inductor is first in a charging state and then in a discharging state, causing the current flowing through the inductor to first increase and then decrease. When the current flowing through the inductor is disturbed, that is, when the peak point of the current flowing through the inductor deviates from the expected value, it is necessary to adjust the peak point of the current flowing through the inductor so that the peak value of the current flowing through the inductor reaches the expected value.

[0062] like Figure 1 and Figure 2 As shown, Figure 1This is a waveform diagram of the current flowing through the inductor in a boost circuit using trailing edge modulation. The solid line represents the expected waveform of the current flowing through the inductor, and the dashed line represents the actual waveform of the current flowing through the inductor. c i represents the expected value of the current flowing through the inductor. s (n) represents the current flowing through the inductor, i peak ΔI represents the peak value of the current flowing through the inductor, ΔI represents the deviation of the valley value of the current flowing through the inductor during the process of adjusting the peak value of the current flowing through the inductor to reach the expected value, m1 is the rate of increase of the current flowing through the inductor when the inductor is in the charging state, and m2 is the rate of decrease of the current flowing through the inductor when the inductor is in the discharging state. Figure 2 This is the switching signal waveform corresponding to the current waveform flowing through the inductor in a boost circuit using trailing edge modulation, where (n-1)T s Representing the (n-1)th period, (n)T s Represents the nth period, (n+1)T s d represents the (n+1)th period. n T s This represents the time during which the switch signal is high in the nth cycle, (1-d n )T s d represents the time during which the switch signal is low in the nth cycle. n+1 T s This represents the time during which the switch signal is high in the (n+1)th cycle, (1-d n+1 )T s This represents the time during which the switch signal is at a low level in the (n+1)th cycle, wherein the inductor is in a charging state when the switch signal is at a high level and in a discharging state when the switch signal is at a low level.

[0063] according to Figure 1 It can be seen that in a boost circuit using trailing edge modulation, during the current operating cycle, when the current i flowing through the inductor... s (n) When disturbed, i.e., when the peak value of the current flowing through the inductor deviates from the expected value, the peak value of the current flowing through the inductor can be adjusted by regulating the peak value of the current flowing through the inductor, i.e., by regulating the peak value of the current flowing through the inductor and the time to reach the peak value, so that the peak value of the current flowing through the inductor reaches the expected value. It is known that the peak value of the current flowing through the inductor and the time to reach the peak value are related to the time the inductor is in the charging state, so the peak value of the current flowing through the inductor can be adjusted by regulating the time the inductor is in the charging state. However, in the current working cycle, when the time the inductor is in the charging state changes, the time the inductor is in the discharging state also changes, which in turn changes the valley value of the current flowing through the inductor in the current working cycle, causing a deviation ΔI in the valley value of the current flowing through the inductor.

[0064] Normally, the rate of increase of the current flowing through the inductor is related to the supply voltage of the boost circuit, and the rate of decrease of the current flowing through the inductor is related to the difference between the supply voltage and the output voltage of the boost circuit. Since the supply voltage of the boost circuit remains constant, when the output voltage of the boost circuit is stable, that is, when the boost circuit is working normally, the rate of increase of the current flowing through the inductor in each working cycle is approximately the same, and the rate of decrease of the current flowing through the inductor is approximately the same. Therefore, when the current flowing through the inductor is disturbed, and this disturbance is eliminated by adjusting the peak point of the current flowing through the inductor, the valley value of the current flowing through the inductor will deviate. Since the rate of increase and rate of decrease of the current flowing through the inductor are approximately the same in each operating cycle, when the valley value of the current flowing through the inductor deviates, it will affect the peak value of the current flowing through the inductor. The peak value of the current flowing through the inductor needs to be adjusted again to match the expected value, which will again cause a deviation in the valley value of the current flowing through the inductor. Thus, the boost circuit that eliminates the disturbance of the current flowing through the inductor by adjusting the peak point of the current flowing through the inductor—that is, the boost circuit using trailing edge modulation—will cause a deviation in the valley value of the current flowing through the inductor in each operating cycle. Furthermore, combined with… Figure 1 and Figure 2 It can be seen that when the charging time of the inductor is adjusted so that the peak value of the current flowing through the inductor is the same as the expected value, when the charging time of the inductor exceeds half of the working cycle of the boost circuit, the deviation of the valley value of the current flowing through the inductor will become larger and larger, thus forming subharmonic oscillation and affecting the normal operation of the boost circuit.

[0065] Based on this, embodiments of this application provide a boost circuit, such as... Figure 3 As shown, the boost circuit includes:

[0066] The working circuit includes a first resistor R2, an inductor L, a capacitor C, and a load R1. The first resistor R2 and the inductor L are connected in series, and the first terminal of the first resistor R2 is the input terminal of the boost circuit, receiving the supply voltage V from the boost circuit. IN The second terminal is connected to the first terminal of the inductor L, and the second terminal of the inductor L is grounded through the first switch S1; the first terminal of the capacitor C is connected to the second terminal of the inductor L through the second switch S2, and the second terminal is grounded; the first terminal of the load R1 is connected to the second terminal of the capacitor C, and the second terminal is grounded; the voltage difference across the load R1 is the output voltage V of the boost circuit. OUT ;

[0067] Control circuit 100, the first input terminal INT1 of the control circuit 100 receives the output voltage V of the boost circuit.OUT The second input terminal INT2 receives the power supply voltage V of the boost circuit. IN The third input terminal INT3 receives the voltage difference ΔV across the first resistor R2, based on the output voltage V of the boost circuit. OUT The power supply voltage V of the boost circuit IN The voltage difference ΔV across the first resistor R2 generates a control signal to control the conduction state and conduction time of the first switch S1 and the second switch S2.

[0068] Optionally, in one embodiment of this application, the supply voltage is provided by a power supply VDD to power the boost circuit; the inductor is an energy storage inductor, which is connected to the power supply through the first resistor to receive the supply voltage, thereby enabling the inductor to be charged by the power supply, i.e., the inductor stores energy through the power supply; the first terminal of the capacitor is connected to the second terminal of the inductor through the first switch, and the first terminal of the load is connected to the first terminal of the capacitor, i.e., the first terminal of the load is connected to the second terminal of the inductor through the first terminal of the capacitor, so that the inductor can discharge to the capacitor and the load, wherein the voltage difference across the load is the output voltage of the boost circuit. It should be noted that in other embodiments of this application, the supply voltage can also be provided by other power supply devices besides the power supply, and this application does not limit this, depending on the specific circumstances.

[0069] It should be noted that, in specific operation, the boost circuit provided in this application embodiment includes an inductor, a first switch, and a power supply device in its charging path, and an inductor, a second switch, a capacitor, a load, and a power supply device in its discharging path. Therefore, the boost circuit can control the charging and discharging states of the inductor, and the duration of the inductor's charging and discharging states, by controlling the on and off states of the first and second switches and the duration of their on and off states. Specifically, in this application embodiment, when the first switch is on and the second switch is off, the inductor is in a charging state, i.e., the power supply device charges the inductor; when the first switch is off and the second switch is on, the inductor is in a discharging state, i.e., the inductor discharges to the capacitor and the load.

[0070] Optionally, in one embodiment of this application, the first switch is a field-effect transistor or a bipolar transistor, and the second switch is a field-effect transistor or a bipolar transistor, but this application does not limit this and it depends on the specific circumstances.

[0071] Continue as Figure 3 As shown, in a specific embodiment of this application, the first input terminal of the control circuit 100 is connected to the first terminal of the load R1 to input the output voltage of the boost circuit, the second input terminal is connected to the output terminal of the power supply device to input the power supply voltage, and the third input terminal is connected to both ends of the first resistor R2, that is, the third input terminal is connected to the first end and the second end of the first resistor R2 to input the voltage difference across the first resistor R2. This enables the control circuit 100 to generate a control signal based on the output voltage of the boost circuit, the power supply voltage of the boost circuit, and the voltage difference across the first resistor R2, and output it to the control terminal of the first switch S1 and the control terminal of the second switch S2 to control the on and off states of the first switch S1 and the second switch S2 and the on and off times of the first switch S1 and the second switch S2, thereby controlling the charging and discharging states of the inductor L and the time during which the inductor L is in the charging and discharging states.

[0072] Based on the above embodiments, in this embodiment, the control signal generated by the control circuit can, in each working cycle of the boost circuit, first make the first switch open and the second switch on, then make the first switch on and the second switch open. That is, in each working cycle of the boost circuit, the control signal generated by the control circuit makes the inductor first in a discharging state and then in a charging state. In other words, in each working cycle of the boost circuit, the control signal generated by the control circuit makes the current flowing through the inductor first decrease and then increase.

[0073] As mentioned above, when the inductor is in a charging state (i.e., the current flowing through the inductor increases), the rate of increase of the current flowing through the inductor is related to the supply voltage of the boost circuit. When the inductor is in a discharging state (i.e., the current flowing through the inductor decreases), the rate of decrease of the current flowing through the inductor is related to the difference between the output voltage of the boost circuit and the supply voltage of the boost circuit. Since the supply voltage of the boost circuit remains constant, when the output voltage of the boost circuit stabilizes (i.e., when the boost circuit is working normally), in each operating cycle of the boost circuit, when the inductor is in a charging state (i.e., the current flowing through the inductor increases), the rate of increase of the current flowing through the inductor is approximately the same; when the inductor is in a discharging state (i.e., the current flowing through the inductor decreases), the rate of decrease of the current flowing through the inductor is approximately the same.

[0074] Furthermore, in each operating cycle of the boost circuit, the valley point of the current flowing through the inductor is related to the time the inductor is in the discharging state, that is, the valley point of the current flowing through the inductor and the time when the current flowing through the inductor reaches the valley point are related to the time when the inductor is in the discharging state, and the peak point of the current flowing through the inductor is related to the time when the inductor is in the charging state, that is, the peak point of the current flowing through the inductor and the time when the current flowing through the inductor reaches the peak point are related to the time when the inductor is in the charging state.

[0075] In the boost circuit provided in this application embodiment, the control signal generated by the control circuit can control the duration of the first switch and the second switch being in the on and off states, thereby controlling the duration of the inductor being in the charging and discharging states. Therefore, in the boost circuit provided in this application embodiment, the control signal generated by the control circuit can control the duration of the inductor being in the charging and discharging states by adjusting the duration of the first switch and the second switch being in the on and off states, thereby adjusting the valley and peak points of the current flowing through the inductor in each operating cycle of the boost circuit.

[0076] Specifically, when the current flowing through the inductor is disturbed—that is, when there is a deviation between the peak value of the current flowing through the inductor in the current operating cycle and the expected value of the current flowing through the inductor—the boost circuit provided in this application can determine, based on the deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor, the valley point of the current flowing through the inductor in the current operating cycle that allows the peak value of the current flowing through the inductor to be the same as the expected value of the current flowing through the inductor. In other words, it determines the valley point of the current flowing through the inductor in the current operating cycle that allows the peak value of the current flowing through the inductor to be the same as the expected value of the current flowing through the inductor. When the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, the valley value of the current flowing through the inductor and the time when the current flowing through the inductor reaches the valley value are controlled by the control signal to control the on and off states of the first switch and the second switch and the time in the off and on states, thereby adjusting the time when the inductor is in the discharge state, and further adjusting the valley point of the current flowing through the inductor, so that the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, eliminating the fluctuation of the current flowing through the inductor caused by disturbance.

[0077] In addition, since the rate of decrease of the current flowing through the inductor is approximately the same and the rate of increase of the current flowing through the inductor is approximately the same in each operating cycle of the boost circuit, when the peak point of the current flowing through the inductor is determined, the valley point of the current flowing through the inductor will also be determined. Furthermore, without changing the output voltage of the boost circuit and without considering the influence of external factors, the current flowing through the inductor will not change in subsequent operating cycles. Therefore, when there is a deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor, the boost circuit provided in this application determines the valley point of the current flowing through the inductor by the deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor. This ensures that after the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, the valley point of the current flowing through the inductor will not change in subsequent operating cycles without changing the output voltage of the boost circuit or considering the influence of external factors. This avoids subharmonic oscillations caused by fluctuations in the valley point of the current flowing through the inductor, giving the boost circuit better anti-fluctuation capability and thus better stability.

[0078] In summary, the boost circuit provided in this application can adjust the valley point of the current flowing through the inductor to make the peak value of the current flowing through the inductor the same as the expected value of the current flowing through the inductor when the current flowing through the inductor is disturbed. It can also avoid subharmonic oscillations, so that the boost circuit described in the embodiments of this application has good anti-fluctuation capability.

[0079] The following detailed description, through specific embodiments, details the process by which the boost circuit eliminates fluctuations in the current flowing through the inductor caused by disturbances.

[0080] Specifically, such as Figure 4 As shown, Figure 4 This is a waveform diagram of the current flowing through the inductor after the output voltage of the boost circuit stabilizes, and its corresponding switching signal waveform diagram. Here, νc is the expected value of the current flowing through the inductor; is(n) is the current flowing through the inductor in the current cycle; ΔI is the deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor when the current fluctuates; m1 is the slope of the curve showing the change in current flowing through the inductor when the inductor is in a charging state, i.e., the rate of increase of the current flowing through the inductor when the inductor is in a charging state; m2 is the slope of the curve showing the change in current flowing through the inductor when the inductor is in a discharging state, i.e., the rate of decrease of the current flowing through the inductor when the inductor is in a discharging state; (n-1)-th Cycle represents the (n-1)th cycle; n-th Cycle represents the nth cycle; Dn-1 T s This represents the time during the (n-1)th cycle when the first switch is in the off state and the second switch is in the on state, causing the inductor to be in the discharging state; (1-D) n-1 )T s D represents the time during the (n-1)th cycle when the first switch is in the on state and the second switch is in the off state, causing the inductor to be in the charging state; n T s This represents the time during the nth cycle when the first switch is in the off state and the second switch is in the on state, causing the inductor to be in the discharging state; (1-D) n )T s This represents the time during which the first switch is in the on state and the second switch is in the off state in the nth cycle, resulting in the inductor being in the charging state.

[0081] Depend on Figure 4 It can be seen that when the boost circuit detects a disturbance in the current flowing through the inductor causing a fluctuation ΔI during the current operating cycle, that is, when the peak value of the current flowing through the inductor deviates from the expected value of the current flowing through the inductor by ΔI, the boost circuit can determine the valley point of the current flowing through the inductor when the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, based on the deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor. In other words, it can determine the valley value of the current flowing through the inductor and the time to reach the valley value when the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor. Specifically, after the boost circuit determines the valley point of the current flowing through the inductor by the deviation between the peak value of the current flowing through the inductor and the expected value of the current flowing through the inductor, the boost circuit will adjust the time when the inductor is in the discharge state through the control circuit to adjust the valley point of the current flowing through the inductor, so that the peak value of the current flowing through the inductor is the same as the expected value of the current flowing through the inductor, thereby eliminating the fluctuation of the current flowing through the inductor caused by disturbance.

[0082] And from Figure 4It can also be seen that, by adjusting the valley point of the current flowing through the inductor, the boost circuit ensures that the peak value of the current flowing through the inductor is the same as the expected value, thus eliminating the fluctuations in the current flowing through the inductor caused by disturbances. Under the condition that the output voltage of the boost circuit remains unchanged and external factors are not considered, the valley point of the current flowing through the inductor will not change in subsequent operating cycles. Compared with boost circuits using trailing edge modulation, the boost circuit provided in this embodiment, while eliminating the fluctuations in the current flowing through the inductor caused by disturbances, also ensures that the valley point of the current flowing through the inductor does not change in subsequent operating cycles, without changing the output voltage of the boost circuit or considering external factors. This avoids subharmonic oscillations caused by fluctuations in the valley point of the current flowing through the inductor, giving the boost circuit better anti-fluctuation capability.

[0083] Based on the above embodiments, in one embodiment of this application, in order for the control circuit to generate control signals to control the on and off states of the first switch and the second switch, as well as the duration of the first switch and the second switch being in the on and off states, thereby controlling the charging and discharging states of the inductor, such as... Figure 5 As shown, the control circuit includes:

[0084] The calibration module (PID) 101 is provided with the output voltage of the boost circuit as input and a reference voltage as reference. The calibration module 101 outputs a reference current based on the output voltage of the boost circuit and the reference voltage.

[0085] The control module 102 has the reference current input at its first input terminal, the output voltage of the boost circuit input at its second input terminal, the supply voltage input at its third input terminal, and the voltage difference across the first resistor input at its fourth input terminal. Based on the reference current, the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor, the control module 102 outputs a duty cycle signal.

[0086] The pulse width modulation module (PWM) 103 receives the duty cycle signal at its first input terminal, and generates a corresponding pulse signal according to the duty cycle signal. The pulse signal is then input to the control terminal of the first switch and the control terminal of the second switch to control the conduction state and conduction time of the first switch and the second switch.

[0087] Specifically, in this embodiment, the input terminal of the calibration module is connected to the first terminal of the load to input the output voltage of the boost circuit. A reference voltage is also provided in the calibration module so that it outputs a reference current based on the input output voltage of the boost circuit and the reference voltage. The first input terminal of the control module is connected to the output terminal of the calibration module to input the reference current. The second input terminal is connected to the first terminal of the load R1 to input the output voltage of the boost circuit. The third input terminal is connected to the input terminal of the boost circuit to input the supply voltage. The fourth input terminal is connected to both ends of the first resistor R2. That is, the fourth input terminal of the control module is connected to both the first and second terminals of the first load R2 to control the voltage across the first resistor R2. The differential pressure is input to the control module so that the control module can output a duty cycle signal based on the reference current, the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor. The first input terminal of the pulse width modulation module is connected to the output of the control module and inputs the duty cycle signal so that the pulse width modulation module can generate and output a corresponding pulse signal according to the duty cycle signal. The pulse signal is the control signal generated by the control circuit. The output terminal of the pulse width modulation module is connected to the control terminals of the first switch and the second switch so that the pulse signal can control the on and off states of the first switch and the second switch and the on and off times of the first switch and the second switch.

[0088] Optionally, in one embodiment of this application, the calibration module is a D-PID calibration module, that is, a calibration module that uses digital proportion, integral, and differential calculation methods.

[0089] It should be noted that, typically, when a calibration module is applied to a system, the system can set preset data in the calibration module according to actual needs and input actual data into the calibration module. When there is a difference between the actual data and the preset data, i.e., the actual data is different from the preset data and the system has an error, the calibration module will perform proportional, integral, and differential operations on the difference between the actual data and the preset data to reduce the difference between the actual data and the preset data until it becomes zero, thus making the actual data equal to the preset data and eliminating the system error. In this embodiment, the boost circuit includes a calibration module. The calibration module can perform proportional, integral, and differential operations on the difference between the output voltage of the boost circuit and the reference voltage to make the output voltage of the boost circuit equal to the reference voltage, eliminating the error of the boost circuit, and making the actual value of the reference current of the boost circuit the same as the expected value of the reference current of the boost circuit.

[0090] Since the reference current is used to obtain the duty cycle signal, and the duty cycle signal enables the pulse width modulation module to generate a corresponding pulse signal, controlling the on / off state and the on / off time of the first and second switches, thereby controlling the operation of the boost circuit. Therefore, in this embodiment, the boost circuit utilizes the calibration module to eliminate the difference between the output voltage of the boost circuit and the reference voltage, obtaining a reliable reference current. This helps to obtain an accurate duty cycle signal, thereby enabling the pulse signal generated based on the duty cycle signal to accurately control the operation of the boost circuit, resulting in better stability of the boost circuit.

[0091] Based on the above embodiments, in one embodiment of this application, the calibration module includes: a calibration unit, an adjustment unit, and a calculation unit. The calibration unit obtains the difference between the output voltage of the boost circuit and the reference voltage based on the output voltage of the boost circuit and the reference voltage. The adjustment unit adjusts the integral parameter of the calibration module based on the difference between the output voltage of the boost circuit and the reference voltage. When the difference between the output voltage of the boost circuit and the reference voltage is less than a first preset value, the current integral parameter of the calibration module is increased. When the difference between the output voltage of the boost circuit and the reference voltage is between the first preset value and a second preset value (including endpoint values), the integral parameter of the calibration module is decreased. The integral parameter of the calibration module is set to 0 when the difference between the output voltage of the boost circuit and the reference voltage is greater than a second preset value, until the difference between the output voltage of the boost circuit and the reference voltage is no greater than the second preset value. Then, the integral parameter of the calibration module is adjusted according to the relationship between the difference between the output voltage of the boost circuit and the reference voltage and a first preset value. Based on the integral parameter of the calibration module, the calculation unit performs proportional, integral, and differential operations on the difference between the output voltage of the boost circuit and the reference voltage, and outputs the reference current so that the calibration module can output the reference current according to the output voltage of the boost circuit and the reference voltage.

[0092] It should be noted that when the calibration module calculates and eliminates the difference between the actual data and the preset data, the integration parameter of the calibration module is related to the difference between the actual data and the preset data. Specifically, when the difference between the actual data and the preset data is large, in order to ensure calibration accuracy, a longer integration time is required when integrating the difference between the actual data and the preset data to eliminate the difference, i.e., a smaller integration parameter is used. When the difference between the actual data and the preset data is small, the calibration accuracy is high, and in order to improve the system response speed, a shorter integration time can be achieved when integrating the difference between the actual data and the preset data to eliminate the difference, i.e., a larger integration parameter is used.

[0093] Therefore, based on the above embodiments, in one embodiment of this application, in order to improve the calibration accuracy and response speed of the boost circuit, the adjustment unit in the calibration module can adjust the integral parameter of the calibration module based on the difference between the output voltage of the boost circuit and the reference voltage. Specifically, when the difference between the output voltage of the boost circuit and the reference voltage is less than a first preset value, it indicates that the difference between the output voltage of the boost circuit and the reference voltage is small, that is, the error of the boost circuit is small. Therefore, in the process of the calibration module calculating and outputting the reference current based on the difference between the output voltage of the boost circuit and the reference voltage, the integral parameter of the calibration module can be adjusted by the adjustment unit to reduce the integration time of the calibration module, that is, to increase the current integral parameter of the calibration module, so that the calibration module can improve the response speed of the boost circuit without affecting the calibration accuracy.

[0094] When the difference between the output voltage of the boost circuit and the reference voltage is between a first preset value and a second preset value, including the endpoint value, it indicates that the difference between the output voltage of the boost circuit and the reference voltage is relatively large. In order to ensure the calibration accuracy of the boost circuit, during the process of the calibration module calculating the difference between the output voltage of the boost circuit and the reference voltage to obtain and output the reference current, it is necessary to adjust the integral parameter of the calibration module through the adjustment unit, increase the integration time of the calibration module, that is, reduce the current integration parameter of the calibration module, so that the calibration module can ensure the calibration accuracy of the boost circuit and output a reliable reference current of the boost circuit while eliminating errors.

[0095] When the difference between the output voltage of the boost circuit and the reference voltage is greater than a second preset value, it indicates that the difference is too large. In this case, integrating the difference using the calibration module will cause significant oscillations in the boost circuit, reducing its stability. To prevent these oscillations from affecting its stability, when the difference between the output voltage and the reference voltage is greater than the second preset value, the integration parameter of the calibration module needs to be set to 0 via the adjustment unit. This means disabling the integration option of the calibration module until the difference is no greater than the second preset value (i.e., the difference is less than or equal to the second preset value). Then, based on the relationship between the difference between the output voltage and the reference voltage and a first preset value, the integration parameter of the calibration module is adjusted.

[0096] It should be noted that the application scenario of the boost circuit will also affect the difference between the output voltage of the boost circuit and the reference voltage. Therefore, the boost circuit provided in this embodiment can improve the adaptability of the boost circuit to different application scenarios by adjusting the integral parameters of the calibration module in the calculation process of the difference between the output voltage of the boost circuit and the reference voltage according to the difference between the output voltage of the boost circuit and the reference voltage.

[0097] Optionally, in one embodiment of this application, the first preset value is 0.2V and the second preset value is 2V, but this application does not limit this and it depends on the specific circumstances.

[0098] The following section uses the first preset value of 0.2V and the second preset value of 2V as examples to explain in detail how to adjust the integral parameters in the calibration module's calculation process based on the difference between the output voltage of the boost circuit and the reference voltage.

[0099] Specifically, when the difference between the output voltage of the boost circuit and the reference voltage is less than 0.2V, it indicates that the difference between the output voltage of the boost circuit and the reference voltage is small. Therefore, in the process of the calibration module calculating the difference between the output voltage of the boost circuit and the reference voltage to obtain and output the reference current, the integration time of the calibration module can be reduced, that is, the current integration parameter of the calibration module can be increased, so that the calibration module can ensure the calibration accuracy of the boost circuit and output a reliable reference current of the boost circuit while eliminating errors.

[0100] When the difference between the output voltage of the boost circuit and the reference voltage is between 0.2V and 2V (including the endpoint value), it indicates that the difference between the output voltage of the boost circuit and the reference voltage is relatively large. In order to ensure the calibration accuracy of the boost circuit, in the process of the calibration module calculating the difference between the output voltage of the boost circuit and the reference voltage to obtain and output the reference current, it is necessary to increase the integration time of the calibration module, that is, reduce the current integration parameter of the calibration module, so that the calibration module can ensure the calibration accuracy of the boost circuit and output a reliable reference current of the boost circuit while eliminating errors.

[0101] When the difference between the output voltage of the boost circuit and the reference voltage is greater than 2V, it indicates that the difference is too large. Integrating this difference will cause significant oscillations in the boost circuit, reducing its stability. Therefore, when the difference is greater than 2V, the integration parameter of the calibration module should be set to 0 (i.e., the integration option should be disabled) until the difference is no greater than 2V. Then, adjust the integration parameter of the calibration module based on whether the difference is greater than or equal to 0.2V or less than 0.2V, and use the calibration module to calculate the difference between the output voltage and the reference voltage to output the reference current.

[0102] Based on the above embodiments, in a specific embodiment of this application, the following continues... Figure 5 As shown, the control module (Control) The first input terminal of the control module 102 is connected to the output terminal of the calibration module 101, so that the reference current can be input into the control module. The second input terminal of the control module 102 is connected to the first terminal of the load R1, so that the output voltage of the boost circuit can be input into the control module. The third input terminal of the control module 102 is connected to the input terminal of the boost circuit, so that the supply voltage can be input into the control module 102. The fourth input terminal of the control module 102 is connected to both ends of the first resistor R2, that is, the fourth input terminal of the control module 102 is connected to the first end and the second end of the first resistor R2, so that the voltage difference across the first resistor R2 can be input into the control module 102. Thus, the control module 102 can calculate the duty cycle signal based on the reference current, the output voltage of the boost circuit, the supply voltage, and the voltage difference across the first resistor R2. The duty cycle signal will be used to generate the control signal to control the on and off states of the first switch S1 and the second switch S2. It should be noted that, in this embodiment of the application, in order for the control module to obtain the duty cycle signal, it is also necessary to set the inductance value of the inductor and the working cycle time of the boost circuit in the control module.

[0103] It should be noted that the control module calculates the duty cycle signal D(n) based on the reference current, the output voltage of the boost circuit, the supply voltage, the voltage difference across the first resistor, the inductance value of the inductor, and the operating cycle time of the boost circuit. The calculation formula is as follows:

[0104]

[0105]

[0106]

[0107] Where, ν c I is the reference current output by the calibration module. s (n) represents the current flowing through the inductor in the current cycle of the boost circuit, V IN V is the supply voltage. OUT The output voltage of the boost circuit is L, where L is the inductance of the inductor, and T is T. s The duty cycle time is the operating cycle time of the boost circuit. In this embodiment, the control module can use the above calculation formula to calculate the duty cycle signal based on the reference current, the output voltage of the boost circuit, the supply voltage, the voltage difference across the first resistor, the inductance value of the inductor, and the operating cycle time of the boost circuit.

[0108] It should also be noted that since the current flowing through the first resistor and the current flowing through the inductor are the same, and the resistance of the first resistor is a set value, the current value flowing through the inductor can be determined when the voltage difference across the first resistor is determined. Therefore, when the boost circuit calculates the duty cycle signal using the aforementioned formula, it can connect the fourth input terminal of the control module to the first and second terminals of the first resistor, respectively, to input the voltage difference across the first resistor into the control module for calculating the duty cycle signal. It should also be noted that the embodiment of this application does not limit the resistance value of the first resistor; it depends on the specific circumstances.

[0109] Based on the above embodiments, in the embodiments of this application, the following continues... Figure 5 As shown, the first input terminal of the pulse width modulation (PWM) module 103 is connected to the output terminal of the control module 102 to input the duty cycle signal and generate a corresponding pulse signal according to the duty cycle signal. The pulse signal is the control signal generated by the control circuit. The output terminal of the pulse width modulation module 103 is connected to the control terminal of the first switch S1 and the control terminal of the second switch S2 to output the pulse signal generated therefrom to the control terminals of the first switch S1 and the second switch S2, thereby controlling the on and off states of the first switch S1 and the second switch S2 and the on and off times of the first switch S1 and the second switch S2.

[0110] It should be noted that in this embodiment, the control module adopts a leading-edge modulation algorithm. When the duty cycle signal output by the control module is input into the pulse width modulation module, the pulse signal generated by the pulse width modulation module first generates a low-level part, and then generates a high-level part. This allows the first switch to be in the off state and the second switch to be in the on state, and then the first switch to be in the on state and the second switch to be in the off state. This means that the inductor is first in the discharging state and then in the charging state, that is, the current flowing through the inductor first decreases and then increases. This allows the fluctuation of the current flowing through the inductor to be eliminated by adjusting the valley point of the current flowing through the inductor when the current is disturbed. It also avoids subharmonic oscillations, giving the boost circuit better anti-fluctuation capability.

[0111] It should also be noted that, in order for the low-level portion of the pulse signal to control the first switch to be in the off state and the second switch to be in the on state, and for the high-level portion of the pulse signal to control the first switch to be in the on state and the second switch to be in the off state, optionally, in one embodiment of this application, the first switch is an N-type field-effect transistor and the second switch is a P-type field-effect transistor, but this application does not limit this and it depends on the specific situation.

[0112] Specifically, in one embodiment of this application, the boost circuit includes both analog and digital circuits, wherein the operating circuit belongs to the analog circuit section and the control circuit belongs to the digital circuit section. Therefore, in order to input the analog signal from the analog circuit section of the boost circuit to the digital circuit section of the boost circuit, so that the control circuit can generate a control signal, based on any of the above embodiments, in one embodiment of this application, such as... Figure 6 As shown, the boost circuit further includes:

[0113] The first signal conversion module 10 has its input terminal connected to the first terminal of the load R1 and its output terminal connected to the first input terminal INT1 of the control circuit 100, so as to convert the voltage difference across the load R1 from an analog signal into a digital signal and output it to the first input terminal INT1 of the control circuit 100. The second terminal of the load R1 is grounded.

[0114] The second signal conversion module 20 has its input terminal connected to the input terminal of the boost circuit and its output terminal connected to the second input terminal INT2 of the control circuit 100, so as to convert the power supply voltage from an analog signal to a digital signal and output it to the second input terminal INT2 of the control circuit 100.

[0115] The third signal conversion module 30 has its input terminals connected to both ends of the first resistor R2, and its output terminal connected to the third input terminal INT3 of the control circuit 100, so as to convert the voltage difference across the first resistor R2 from an analog signal into a digital signal and output it to the third input terminal INT3 of the control circuit 100.

[0116] Specifically, such as Figure 7 As shown, when the control circuit includes a calibration module 101, a control module 102, and a pulse width modulation module 103, the input terminal of the first signal conversion module 10 is connected to the first terminal of the load R1, and the output terminal is connected to the input terminal of the calibration module 101 and the second input terminal of the control module 102, respectively, so as to convert the voltage difference across the load R1 from an analog signal into a digital signal and output it to the calibration module 101 and the control module 102; the input terminal of the second signal conversion module 20 is connected to the input terminal of the boost circuit, and the output terminal is connected to the control module 102. The third input terminal of the 02 is connected to convert the power supply voltage of the boost circuit from an analog signal to a digital signal and input it into the control module 102; the input terminals of the third signal conversion module 30 are respectively connected to the two ends of the first resistor R2, that is, the input terminals of the third signal conversion module 30 are respectively connected to the first end of the first resistor R2 and the second end of the first resistor R2, and the output terminal is connected to the fourth input terminal of the control module 102 to convert the voltage difference across the first resistor R2 from an analog signal to a digital signal and input it into the control module 102.

[0117] Optionally, in one embodiment of this application, the first signal conversion module includes an analog-to-digital converter (ADC) to convert the output voltage of the boost circuit from an analog signal to a digital signal; the second signal conversion module includes an ADC to convert the power supply voltage of the boost circuit from an analog signal to a digital signal; and the third signal conversion module includes an ADC to convert the power supply voltage of the boost circuit from an analog signal to a digital signal, but this application does not limit this.

[0118] It should be noted that, typically, the range of an analog-to-digital converter (ADC) is relatively small, less than the strength of the analog signal in the analog circuit. Therefore, when the boost circuit includes both analog and digital circuits, and the ADC needs to convert the analog signal into a digital signal, in order to ensure that the strength of the analog signal from the analog circuit does not exceed the range of the ADC and can be input into the ADC, based on the above embodiments, in one embodiment of this application, such as... Figure 8As shown, the working circuit also includes:

[0119] The first voltage divider module 11 includes a second resistor R3 and a third resistor R4 connected in series. The first end of the first voltage divider module 11 is connected to the first end of the load R1, and the second end is grounded. The voltage at the common end of the second resistor R3 and the third resistor R4 is used to characterize the output voltage of the boost circuit, so that the voltage signal input to the input end of the first analog-to-digital converter module 10 is within its range.

[0120] The second voltage divider module 21 includes a fourth resistor R5 and a fifth resistor R6 connected in series. The first end of the second voltage divider module 21 is connected to the input end of the boost circuit, and the second end is grounded. The voltage at the common end of the fourth resistor R5 and the fifth resistor R6 is used to characterize the power supply voltage of the boost circuit, so that the voltage signal input to the input end of the second analog-to-digital converter module 20 is within its range.

[0121] Optionally, in one embodiment of this application, the first voltage divider module includes only two resistors, a second resistor and a third resistor. However, in other embodiments of this application, the first voltage divider module may also include at least three resistors. This application does not limit this, and it depends on the specific circumstances.

[0122] Similarly, the second voltage divider module may include only two resistors, the fourth resistor and the fifth resistor, or it may include at least three resistors, but this application does not limit this and it depends on the specific situation.

[0123] It should be noted that since each pulse signal period corresponds to a duty cycle signal, and the pulse signal first generates a low-level portion and then a high-level portion, if the sum of the operating clocks of the first signal conversion module, the second signal conversion module, the third signal conversion module, and the control circuit is greater than the width of the low level of the pulse signal, the duty cycle signal will not be able to update within the current period, thus failing to adjust the operating state of the boost circuit and causing instability in the boost circuit. Therefore, in one embodiment of this application, in any period of the pulse signal, the sum of the operating clocks of the first signal conversion module, the second signal conversion module, the third signal conversion module, and the control circuit is less than the width of the low level of the pulse signal in the current period, so that the duty cycle signal can be updated within the current period to modulate the boost circuit and avoid instability in the boost circuit due to the duty cycle signal not being able to update within the current period.

[0124] It should also be noted that, in this embodiment, the first signal conversion module, the second signal conversion module, and the third signal conversion module constitute the signal conversion module of the boost circuit. Furthermore, the first signal conversion module, the second signal conversion module, and the third signal conversion module operate simultaneously, and their operating clocks are the same. Therefore, the operating clock of the boost circuit's signal conversion module will be simultaneously the same as the operating clocks of the first, second, and third signal conversion modules. This ensures that the sum of the operating clocks of the boost circuit's signal conversion module and the control circuit is simultaneously the same as the sum of the operating clocks of the first, second, and third signal conversion modules, the second, and third signal conversion modules.

[0125] Specifically, such as Figure 9 As shown, Figure 9 This is a timing diagram of the boost circuit in operation according to an embodiment of this application. CLK_ADC is a schematic diagram showing the working clocks of the first signal conversion module, the second signal conversion module, and the third signal conversion module; that is, CLK_ADC is a schematic diagram showing the working clock of the signal conversion module of the boost circuit; CLK_DIG is a schematic diagram showing the working clock of the control circuit in the boost circuit; Dn is the duty cycle signal; Cnt is a counter (outputting a new duty cycle signal when counting to m); PWM is a waveform diagram of the pulse signal generated by the pulse width modulation module; N and N+1 represent the Nth cycle and the (N+1)th cycle, respectively; T ADC +T LOGIC This is the sum of the delay of the signal conversion module of the boost circuit and the delay of the control circuit.

[0126] according to Figure 9 As can be seen, in the boost circuit provided in this application embodiment, the sum of the delay of the signal conversion module of the boost circuit and the delay of the control circuit is less than the width of the low level of the pulse signal output by the pulse width modulation module. This ensures that the duty cycle signal can be updated in each pulse signal cycle, thereby adjusting the boost circuit and preventing instability of the boost circuit due to the duty cycle signal not being updated in the current cycle.

[0127] It should be noted that, in the embodiments of this application, the operating clock of the control circuit is an integer multiple of the operating clocks of the first signal conversion module, the second signal conversion module, and the third signal conversion module, and the low-level width of the pulse signal generated by the pulse width modulation module is an integer multiple of the operating clocks of the first signal conversion module, the second signal conversion module, the third signal conversion module, and the control circuit.

[0128] It should also be noted that, because the resolution of the pulse width modulation module is lower than that of the analog-to-digital conversion module, the boost circuit may experience limit cycle oscillations, resulting in noise and affecting its normal operation. Therefore, based on any of the above embodiments, in one embodiment of this application, to suppress the limit cycle oscillations in the boost circuit, such as... Figure 10 As shown, the control circuit further includes a noise shaping module (delta-sigma modulator, abbreviated as DSM) 104. The input terminal of the noise shaping module 104 receives the duty cycle signal, which is used to perform noise shaping on the duty cycle signal, and outputs the noise-shaped duty cycle signal to the pulse width modulation module 103. Specifically, in this embodiment, the input terminal of the noise shaping element is connected to the output terminal of the control module to input the duty cycle signal into the noise shaping module, thereby performing noise shaping on the duty cycle signal and suppressing the limiting cycle oscillation phenomenon in the boost circuit. Furthermore, the output terminal of the noise shaping module is connected to the first input terminal of the pulse width modulation module to input the noise-shaped duty cycle signal into the pulse width modulation module. It should be noted that using a noise shaping module for noise shaping is a well-known technique in the art, and the working process of the noise shaping module will not be described here.

[0129] Furthermore, during the operation of the boost circuit, low-frequency noise has a greater impact on its operation than high-frequency noise. Therefore, based on the above embodiments, in one embodiment of this application, the noise shaping module is further used to shift low-frequency noise below a preset frequency to the frequency domain of high-frequency noise above or equal to the preset frequency, thereby reducing low-frequency noise and thus reducing its impact on the boost circuit. It should be noted that the specific value of the preset frequency is not limited in this application embodiment and depends on the specific circumstances.

[0130] It should also be noted that the output voltage of the digital circuit is lower than the operating voltage of the analog circuit, and the pulse width modulation module belongs to the digital circuit section. Therefore, in order for the pulse signal generated by the pulse width modulation module to drive the first switch and the second switch, based on any of the above embodiments, in one embodiment of this application, such as... Figure 11 As shown, the boost circuit also includes a level shift module 105. The input terminal of the level shift module 105 receives the pulse signal and is used to convert the voltage of the pulse signal from a first voltage domain to a second voltage domain. The pulse signal converted from the first voltage domain to the second voltage domain is output to the control terminal of the first switch S1 and the control terminal of the second switch S2. The voltage in the second voltage domain is greater than the voltage in the first voltage domain.

[0131] Specifically, in this embodiment, the input terminal of the level shifting module is connected to the output terminal of the pulse width modulation module, so that the level shifting module can convert the pulse signal from the first voltage domain to the second voltage domain. The output terminal of the level shifting module is connected to the control terminal of the first switch S1 and the control terminal of the second switch S2, respectively. The voltage in the first voltage domain is greater than the voltage in the second voltage domain, so that the pulse signal converted from the first voltage domain to the second voltage domain can be input to the control terminals of the first switch and the second switch, driving the first switch S1 and the second switch S2, thereby controlling the on and off states of the first switch S1 and the second switch S2 and the time they are in the on and off states, and thus controlling the charging and discharging of the inductor L.

[0132] It should be noted that during the operation of the boost circuit, the current flowing through the inductor may exceed the maximum limit or reverse, affecting the normal operation of the boost circuit. Therefore, based on any of the above embodiments, in one embodiment of this application, such as Figure 12 As shown, the control circuit further includes a current limiting module (I Limit) 106. The input terminal of the current limiting module 106 receives the current flowing through the inductor L and is used to limit the current flowing through the inductor L. Specifically, in this embodiment, the input terminal of the current limiting module is connected to the output terminal of the third signal conversion module 30 to input the current flowing through the inductor into the current limiting module, and the output terminal of the current limiting module is connected to the second input terminal of the pulse width modulation module to limit the current flowing through the inductor, so as to prevent the current flowing through the inductor from exceeding its maximum limit range and from reverse backflow.

[0133] It should be noted that, as mentioned above, the current flowing through the inductor can be determined based on the voltage difference across the first resistor. Therefore, in this embodiment, the input terminal of the current limiting module is connected to the output terminal of the third signal conversion module to input the voltage difference across the first resistor into the current control module, and to determine whether the current flowing through the inductor exceeds its maximum limit or whether reverse backflow occurs based on the voltage difference across the first resistor.

[0134] Specifically, based on the above embodiments, in one embodiment of this application, when the current flowing through the inductor exceeds its maximum limit, the current limiting module will generate a first feedback signal and input it into the pulse width modulation module, causing the pulse width modulation module to generate a corresponding pulse signal, controlling the first switch to open and the second switch to open, closing the charging path of the inductor and opening the discharging path of the inductor, so that the inductor is in a discharging state, thereby reducing the current flowing through the inductor and preventing the current flowing through the inductor from exceeding its maximum limit and affecting the normal operation of the boost circuit.

[0135] In another embodiment of this application, when the current flowing through the inductor reverses, i.e., when the current flowing through the inductor is less than 0, the current limiting module will generate a second feedback signal and input it into the pulse width modulation module, causing the pulse width modulation module to generate a corresponding pulse signal to control both the first switch and the second switch to be in the open state, i.e., to close the charging and discharging paths of the inductor until the current flowing through the inductor is greater than 0. Then, the charging or discharging path of the inductor is opened according to the actual situation to prevent the current flowing through the inductor from reverse flowing and affecting the normal operation of the boost circuit.

[0136] It should be noted that when the boost circuit is applied in applications with a wide load range, in order to reduce the power consumption of the boost circuit and maintain a stable output voltage, it is necessary to determine the load size of the boost circuit based on the current flowing through the inductor and control the operating mode of the inductor accordingly. Therefore, based on any of the above embodiments, in one embodiment of this application, such as Figure 13 As shown, the control circuit further includes a mode detection module 107. The input terminal of the mode detection module 107 is used to monitor the current flowing through the inductor L and control the working mode of the inductor L according to the current flowing through the inductor L.

[0137] Specifically, in this embodiment, the input terminal of the mode monitoring module is connected to the output terminal of the third signal conversion module 30 to input the current flowing through the inductor L into the mode monitoring module, thereby realizing real-time monitoring of the current flowing through the inductor L, and thus being able to determine the load size of the boost circuit based on the monitored current flowing through the inductor L; in this embodiment, the control module also has a fifth input terminal, and the output terminal of the mode monitoring module is connected to the fifth input terminal of the control module, so that the control module can control the working mode of the inductor based on the current flowing through the inductor L monitored by the mode monitoring module.

[0138] Based on the above embodiments, in one embodiment of this application, the mode monitoring module controls the operating mode of the inductor according to the current flowing through the inductor, specifically as follows: when the current flowing through the inductor is not greater than a third preset value, that is, when the current flowing through the inductor is less than or equal to the third preset value, it indicates that the load of the boost circuit is small at this time, and the inductor is controlled to be in intermittent operating mode, that is, there is a time interval between two adjacent operating cycles of the inductor, so as to reduce power consumption; when the current flowing through the inductor is greater than the third preset value, it indicates that the load of the boost circuit is large at this time, and the inductor is controlled to be in continuous operating mode, that is, there is no time interval between two adjacent operating cycles of the inductor, so as to maintain the output voltage stability of the boost circuit.

[0139] Optionally, in one embodiment of this application, the third preset value is 0.5A, but this application does not limit it and it depends on the specific circumstances.

[0140] It should be noted that, in this embodiment of the application, one charging and discharging cycle of the inductor is one working cycle of the inductor, and this embodiment of the application does not limit the time interval between two adjacent working cycles of the inductor, but depends on the specific circumstances.

[0141] Optionally, based on any of the above embodiments, in one embodiment of this application, when the boost circuit includes an analog circuit section and a digital circuit section, the analog circuit section is implemented by automatic routing using EDA software, and the digital circuit section is implemented by RTL code. This allows the same set of RTL code to reproduce the digital circuit section of the boost circuit when the boost circuit is applied to different application scenarios, and the analog circuit section of the boost circuit to be reproduced by automatic routing using EDA software. This makes the boost circuit provided in this application embodiment highly portable.

[0142] In order to clearly describe the working process of the boost circuit provided in the embodiments of this application, the working process of the boost circuit provided in the embodiments of this application will be described in detail below with reference to the timing diagram of the boost circuit.

[0143] Specifically, such as Figure 14 As shown, Figure 14 This is a timing diagram of the boost circuit provided in the embodiments of this application. Figure 14 As can be seen, the timing diagram of the boost circuit is divided into three parts. The first part of the timing diagram (the part to the left of the first dashed line in the diagram) shows that when the boost circuit is powered on, both the first and second switches are in the open state. However, due to the presence of parasitic diodes in the first and second switches, the current flowing through the inductor and the output voltage V of the boost circuit are affected. out An increase occurs until the output voltage V of the boost circuit increases. out With the power supply voltage V in After they are equal, the output voltage V of the boost circuit is... out Nothing changes, and the current flowing through the inductor becomes 0. It should be noted that during this process, the digital circuitry of the boost circuit does not operate until the boost circuit enters the second part of its operating sequence.

[0144] Continue as Figure 14 As shown, according to the second part of the timing diagram of the boost circuit (the part between the first and second dashed lines in the diagram), it can be seen that the digital part of the boost circuit starts to work at this time, and the output voltage V of the boost circuit... out With reference voltage V ref Before they become equal, the inductor needs to be frequently charged and discharged so that the output voltage V of the boost circuit can be equalized. out It can gradually increase until it matches the reference voltage V. ref The output voltage of the boost circuit is equal to the reference voltage. After the output voltage of the boost circuit is equal to the reference voltage, there is a time interval between two adjacent operating cycles of the inductor, that is, the inductor is in intermittent operating mode. This indicates that the load of the boost circuit is small at this time. In other words, when the load of the boost circuit is small, the inductor is controlled to be in intermittent operating mode to reduce the energy consumption of the boost circuit.

[0145] Continue as Figure 14As shown, according to the third part of the timing diagram of the boost circuit (the part to the right of the second dashed line in the figure), there is no time interval between two adjacent working cycles of the inductor, that is, the inductor is in continuous working mode. This indicates that the load of the boost circuit is large at this time. That is, when the load of the boost circuit is large, the inductor is controlled to be in continuous working mode to maintain the output voltage of the boost circuit stable.

[0146] Accordingly, this application also provides an electronic device, which includes the boost circuit provided in any of the above embodiments. The specific working process of the boost circuit has been described in detail in the above embodiments and will not be repeated here.

[0147] In addition, this application embodiment also provides a control circuit, which is applied to a boost circuit.

[0148] The boost circuit includes a first resistor, an inductor, a capacitor, and a load. The first resistor and the inductor are connected in series, and the first terminal of the first resistor is the input terminal of the boost circuit, receiving the power supply voltage of the boost circuit. The second terminal of the first resistor is connected to the first terminal of the inductor, and the second terminal of the inductor is grounded through a first switch. The first terminal of the capacitor is connected to the second terminal of the inductor through a second switch, and the second terminal is grounded. The first terminal of the load is connected to the first terminal of the capacitor, and the second terminal is grounded. The voltage difference across the load is the output voltage of the boost circuit.

[0149] The control circuit receives the output voltage of the boost circuit at its first input terminal, the supply voltage of the boost circuit at its second input terminal, and the voltage difference across the first resistor of the boost circuit at its third input terminal. Based on the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor, a control signal is generated to control the conduction state and conduction time of the first switch and the second switch of the boost circuit.

[0150] Specifically, in the embodiments of this application, the control signal generated by the control circuit can, in each working cycle of the boost circuit, first cause the first switch of the boost circuit to be in the off state and the second switch of the boost circuit to be in the on state, and then cause the first switch of the boost circuit to be in the on state and the second switch of the boost circuit to be in the off state. That is, in each working cycle of the boost circuit, the control signal generated by the control circuit causes the inductor of the boost circuit to first be in the discharging state and then be in the charging state. In other words, in each working cycle of the boost circuit, the control signal generated by the control circuit causes the current flowing through the inductor of the boost circuit to first decrease and then increase.

[0151] Furthermore, in each operating cycle of the boost circuit, the valley point of the current flowing through the inductor of the boost circuit is related to the time the inductor is in the discharge state. That is, the valley point of the current flowing through the inductor of the boost circuit and the time when the current reaches the valley point are related to the time when the inductor is in the discharge state. The peak point of the current flowing through the inductor of the boost circuit is related to the time when the inductor is in the charging state. That is, the peak point of the current flowing through the inductor of the boost circuit and the time when the current reaches the peak point are related to the time when the inductor is in the charging state.

[0152] The control signal generated by the control circuit provided in this application embodiment can control the on and off times of the first and second switches of the boost circuit, thereby controlling the charging and discharging times of the inductor of the boost circuit. This allows the control signal generated by the control circuit to adjust the on and off times of the first and second switches of the boost circuit, thus controlling the charging and discharging times of the inductor. Consequently, it can adjust the valley and peak points of the current flowing through the inductor in each operating cycle of the boost circuit, enabling the control circuit to... The control circuit adjusts the discharge time of the inductor in the boost circuit, thereby adjusting the trough of the current flowing through the inductor. This ensures that the peak value of the current flowing through the inductor is the same as the expected value, eliminating fluctuations in the current flowing through the inductor caused by disturbances. Furthermore, the control circuit can cause the current flowing through the inductor in the boost circuit with the control circuit to first decrease and then increase, thereby avoiding subharmonic oscillations caused by fluctuations in the trough of the current flowing through the inductor. This gives the boost circuit better anti-fluctuation capability, resulting in better stability. It should be noted that the specific process of the control circuit eliminating fluctuations in the current flowing through the inductor caused by disturbances and avoiding subharmonic oscillations has been described in detail in the boost circuit described in any of the above embodiments and will not be repeated here.

[0153] Based on the above embodiments, in one embodiment of this application, in order to enable the control circuit to generate control signals to control the on and off states of the first and second switches of the boost circuit, as well as the duration of the first and second switches being in the on and off states, thereby controlling the charging and discharging states of the inductor of the boost circuit, the control circuit includes:

[0154] The calibration module (PID) is input to the output voltage of the boost circuit and also includes a reference voltage. Based on the output voltage of the boost circuit and the reference voltage, the calibration module outputs a reference current.

[0155] The control module has the reference current input at its first input terminal, the output voltage of the boost circuit input at its second input terminal, the supply voltage of the boost circuit input at its third input terminal, and the voltage difference across the first resistor of the boost circuit input at its fourth input terminal. Based on the reference current, the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor of the boost circuit, the control module outputs a duty cycle signal.

[0156] The pulse width modulation module (PWM) receives the duty cycle signal at its first input terminal and generates a corresponding pulse signal based on the duty cycle signal. The pulse signal is then input to the control terminals of the first switch and the second switch to control the conduction state and conduction time of the first switch and the second switch of the boost circuit.

[0157] Specifically, in this embodiment, the input terminal of the calibration module is connected to the first terminal of the load of the boost circuit to input the output voltage of the boost circuit. A reference voltage is also provided in the calibration module so that the calibration module outputs a reference current based on the input output voltage of the boost circuit and the reference voltage. The first input terminal of the control module is connected to the output terminal of the calibration module to input the reference current. The second input terminal is connected to the first terminal of the load R1 of the boost circuit to input the output voltage of the boost circuit. The third input terminal is connected to the input terminal of the boost circuit to input the supply voltage of the boost circuit. The fourth input terminal is connected to both ends of the first resistor R2 of the boost circuit. That is, the fourth input terminal of the control module is connected to the first and second terminals of the first load R2 of the boost circuit to input the boost current. The voltage difference across the first resistor R2 of the circuit is input to the control module, enabling the control module to output a duty cycle signal based on the reference current, the output voltage of the boost circuit, the supply voltage of the boost circuit, and the voltage difference across the first resistor of the boost circuit. The first input terminal of the pulse width modulation module is connected to the output of the control module, and the duty cycle signal is input, enabling the pulse width modulation module to generate and output a corresponding pulse signal according to the duty cycle signal. This pulse signal is the control signal generated by the control circuit. The output terminal of the pulse width modulation module is connected to the control terminals of the first switch and the second switch, allowing the pulse signal to control the on / off state and the on / off time of the first and second switches. It should be noted that the specific working processes of the calibration module, the control module, and the pulse width modulation module have been described in detail in the boost circuit of any of the above embodiments, and will not be repeated here.

[0158] Based on the above embodiments, in one embodiment of this application, the control circuit further includes a noise shaping module (delta-sigma modulator, abbreviated as DSM). The input terminal of the noise shaping module DSM receives the duty cycle signal, which is used to perform noise shaping on the duty cycle signal, and outputs the noise-shaped duty cycle signal to the pulse width modulation module. Specifically, in this embodiment, the input terminal of the noise shaping element is connected to the output terminal of the control module to input the duty cycle signal into the noise shaping module, thereby performing noise shaping on the duty cycle signal and suppressing the limiting cycle oscillation phenomenon in the boost circuit. Furthermore, the output terminal of the noise shaping module DSM is connected to the first input terminal of the pulse width modulation module PWM to input the noise-shaped duty cycle signal into the pulse width modulation module PWM.

[0159] In addition, while shaping the duty cycle signal, the noise shaping module can also shift low-frequency noise below a preset frequency to a frequency domain of high-frequency noise greater than or equal to the preset frequency, thereby reducing low-frequency noise and its impact on the boost circuit. It should be noted that the specific value of the preset frequency is not limited in this embodiment and depends on the specific circumstances.

[0160] Based on the above embodiments, in one embodiment of this application, the control circuit further includes a level shift module. The input terminal of the level shift module receives the pulse signal and is used to convert the voltage of the pulse signal from a first voltage domain to a second voltage domain. The pulse signal converted from the first voltage domain to the second voltage domain is output to the control terminals of the first switch and the second switch, wherein the voltage in the second voltage domain is greater than the voltage in the first voltage domain.

[0161] Specifically, in this embodiment, the input terminal of the level shifting module is connected to the output terminal of the pulse width modulation module, so that the level shifting module can convert the pulse signal from the first voltage domain to the second voltage domain. The output terminal of the level shifting module is connected to the control terminals of the first switch and the second switch of the boost circuit, respectively. The voltage in the first voltage domain is greater than the voltage in the second voltage domain, so that the pulse signal converted from the first voltage domain to the second voltage domain can be input to the control terminals of the first switch and the second switch of the boost circuit, driving the first switch and the second switch of the boost circuit, thereby controlling the on and off states of the first switch and the second switch of the boost circuit and the time of being on and off, and thus controlling the charging and discharging of the inductor.

[0162] Based on the above embodiments, in one embodiment of this application, the control circuit further includes a current limiting module (I Limit). The input terminal of the current limiting module receives the current flowing through the inductor and is used to limit the current flowing through the inductor. Specifically, in this embodiment, the input terminal of the current limiting module receives the current flowing through the inductor of the boost circuit, so that the current flowing through the inductor of the boost circuit is input into the current limiting module. The output terminal of the current limiting module is connected to the second input terminal of the pulse width modulation module to limit the current flowing through the inductor, preventing the current flowing through the inductor from exceeding its maximum limit range and preventing reverse backflow. It should be noted that the specific working process of the current limiting module has been described in detail in the boost circuit described in any of the above embodiments and will not be repeated here.

[0163] Based on any of the above implementations, in one embodiment of this application, the control circuit further includes: a mode detection module, wherein the input terminal of the mode detection module receives the current flowing through the inductor, for monitoring the current flowing through the inductor, and controlling the operating mode of the inductor according to the current flowing through the inductor.

[0164] Specifically, in this embodiment, the input terminal of the mode monitoring module receives the current flowing through the inductor, thereby enabling real-time monitoring of the current flowing through the inductor. This allows the module to determine the load of the boost circuit based on the monitored current. The control module also has a fifth input terminal, and the output terminal of the mode monitoring module is connected to this fifth input terminal, allowing the control module to control the inductor's operating mode based on the monitored current. It should be noted that the specific operation of the mode monitoring module has been described in detail in the boost circuit of any of the above embodiments and will not be repeated here.

[0165] In summary, the embodiments of this application provide a boost circuit, an electronic device including the boost circuit, and a control circuit applied to the boost circuit. The boost circuit includes a working circuit and a control circuit. The working circuit includes a first resistor, an inductor, a capacitor, a load, a first switch, and a second switch. The control circuit can generate control signals to control the on and off states of the first and second switches and the duration of their on and off states, thereby controlling the charging and discharging states of the inductor and the duration of their charging and discharging states. This allows the inductor to first be in a discharging state and then in a charging state. When the current flowing through the inductor is disturbed, the peak value of the current flowing through the inductor can be adjusted to make the peak value of the current flowing through the inductor the same as the expected value of the current flowing through the inductor, eliminating the fluctuations in the current flowing through the inductor and avoiding subharmonic oscillations. Therefore, the boost circuit provided by the embodiments of this application has good anti-fluctuation capability.

[0166] Furthermore, the present application provides a boost circuit, an electronic device including the boost circuit, and a control circuit applied to the boost circuit. The boost circuit can also adjust the integral parameters of the calibration module according to the difference between the output voltage of the boost circuit and the reference voltage, thereby obtaining a reliable reference current and improving the response speed and adaptability of the boost circuit to different working scenarios.

[0167] Furthermore, the boost circuit, the electronic device including the boost circuit, and the control circuit applied to the boost circuit provided in this application embodiment are both analog and digital circuits. When the boost circuit is applied in different scenarios, both the digital circuit and the analog circuit can be reproduced, which has strong portability.

[0168] The various parts of this manual are described in a combination of parallel and progressive methods. Each part focuses on the differences between the other parts, and the same or similar parts can be referred to each other.

[0169] The features described above regarding the disclosed embodiments can be substituted or combined with each other to enable those skilled in the art to implement or use this application. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the general principles defined herein can be implemented in other embodiments without departing from the spirit or scope of this application. Therefore, this application is not to be limited to the embodiments shown herein, but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

Claims

1. A boost circuit, characterized by comprising: The application relates to a voltage boosting circuit, which comprises a working circuit and a control circuit. The working circuit comprises a first resistor, an inductor, a capacitor and a load, wherein the first resistor and the inductor are connected in series, the first end of the first resistor is the input end of the voltage boosting circuit, the power supply voltage of the voltage boosting circuit is input into the first end of the first resistor, the second end of the first resistor is connected with the first end of the inductor, the second end of the inductor is connected with the ground through a first switch, the first end of the capacitor is connected with the second end of the inductor through a second switch, and the second end of the capacitor is connected with the ground; the first end of the load is connected with the first end of the capacitor, and the second end of the load is connected with the ground; and the voltage difference between the two ends of the load is the output voltage of the voltage boosting circuit. The first input end of the control circuit is connected with the output voltage of the voltage boosting circuit, the second input end is connected with the power supply voltage of the voltage boosting circuit, the third input end is connected with the voltage difference between the two ends of the first resistor, and the control circuit generates a control signal based on the output voltage of the voltage boosting circuit, the power supply voltage of the voltage boosting circuit and the voltage difference between the two ends of the first resistor, so as to control the conduction state and the conduction time of the first switch and the second switch. The control signal generated by the control circuit can make the first switch be in the off state and the second switch be in the on state first, and then make the first switch be in the on state and the second switch be in the off state in each working cycle of the voltage boosting circuit, so that the control signal generated by the control circuit makes the inductor be in the discharging state first and then be in the charging state in each working cycle of the voltage boosting circuit.

2. The boost circuit of claim 1, wherein, The control circuit comprises a calibration module, a control module and a pulse width modulation module. The input end of the calibration module is connected with the output voltage of the voltage boosting circuit, and a reference voltage is arranged in the calibration module; the calibration module outputs a reference current based on the output voltage of the voltage boosting circuit and the reference voltage. The first input end of the control module is connected with the reference current, the second input end is connected with the output voltage of the voltage boosting circuit, the third input end is connected with the power supply voltage of the voltage boosting circuit, the fourth input end is connected with the voltage difference between the two ends of the first resistor, and the control module outputs a duty cycle signal based on the reference current, the output voltage of the voltage boosting circuit, the power supply voltage of the voltage boosting circuit and the voltage difference between the two ends of the first resistor. The first input end of the pulse width modulation module is connected with the duty cycle signal, the pulse width modulation module generates a corresponding pulse signal according to the duty cycle signal, and outputs the pulse signal to the control end of the first switch and the control end of the second switch, so as to control the conduction state and the conduction time of the first switch and the second switch.

3. The boost circuit of claim 2, wherein, The calibration module comprises a calibration unit. The calibration unit obtains the difference between the output voltage of the voltage boosting circuit and the reference voltage based on the output voltage of the voltage boosting circuit and the reference voltage. The adjusting unit adjusts the integral parameter of the calibration module based on the difference between the output voltage of the boost circuit and the reference voltage, increases the current integral parameter of the calibration module when the difference between the output voltage of the boost circuit and the reference voltage is less than a first preset value, reduces the current integral parameter of the calibration module when the difference between the output voltage of the boost circuit and the reference voltage is between the first preset value and a second preset value, including the end value, and sets the integral parameter of the calibration module to 0 when the difference between the output voltage of the boost circuit and the reference voltage is greater than the second preset value, until the difference between the output voltage of the boost circuit and the reference voltage is not greater than the second preset value, and then adjusts the integral parameter of the calibration module according to the relationship between the difference between the output voltage of the boost circuit and the reference voltage and the first preset value. The calculating unit performs proportional, integral and differential operations on the difference between the output voltage of the boost circuit and the reference voltage based on the integral parameter of the calibration module, and outputs the reference current.

4. The boost circuit of claim 1, wherein, Further comprising: The first signal conversion module is connected with the first end of the load at the input end and connected with the first input end of the control circuit at the output end. The second signal conversion module is connected with the input end of the boost circuit at the input end and connected with the second input end of the control circuit at the output end. The third signal conversion module is connected with both ends of the first resistor at the input end and connected with the third input end of the control circuit at the output end.

5. The boost circuit of claim 4, wherein, The working circuit further comprises: The first voltage division module comprises a second resistor and a third resistor connected in series, and the first end of the first voltage division module is connected with the first end of the load and the second end is grounded. The second voltage division module comprises a fourth resistor and a fifth resistor connected in series, and the first end of the second voltage division module is connected with the input end of the boost circuit and the second end is grounded.

6. The boost circuit of claim 2, wherein, The control circuit further comprises: The noise shaping module inputs the duty cycle signal at the input end, performs noise shaping on the duty cycle signal, and outputs the noise-shaped duty cycle signal to the pulse width modulation module.

7. The boost circuit of claim 2, wherein, Further comprising: The level shift module inputs the pulse signal at the input end, converts the voltage of the pulse signal from a first voltage domain to a second voltage domain, and outputs the pulse signal converted from the first voltage domain to the second voltage domain to the control end of the first switch and the control end of the second switch, wherein the voltage in the second voltage domain is greater than the voltage in the first voltage domain.

8. The boost circuit of claim 5, wherein, The control circuit further comprises: The current limiting module inputs the current flowing through the inductor at the input end, and limits the current flowing through the inductor.

9. The boost circuit of claim 5, wherein, The control circuit further comprises: A mode monitoring module, an input terminal of the mode monitoring module inputs a current flowing through the inductor, and the mode monitoring module is configured to monitor the current flowing through the inductor and control the operation mode of the inductor according to the current flowing through the inductor.

10. The boost circuit of claim 9, wherein, The mode monitoring module is configured to control the operation mode of the inductor according to the current flowing through the inductor, and specifically configured to: control the inductor to be in an intermittent operation mode when the current flowing through the inductor is not greater than a third preset value; control the inductor to be in a continuous operation mode when the current flowing through the inductor is greater than the third preset value.

11. An electronic device, comprising: The boost circuit according to any one of claims 1-10.

12. A control circuit, characterized by The boost circuit comprises a first resistor, an inductor, a capacitor and a load, wherein the first resistor and the inductor are connected in series, a first end of the first resistor is an input terminal of the boost circuit, and an input power supply voltage of the boost circuit is input to the first end of the first resistor, a second end of the first resistor is connected to a first end of the inductor, a second end of the inductor is connected to ground through a first switch, a first end of the capacitor is connected to the second end of the inductor through a second switch, and a second end of the capacitor is connected to ground, a first end of the load is connected to the first end of the capacitor, and a second end of the load is connected to ground, and a voltage difference between the first end and the second end of the load is an output voltage of the boost circuit. The control circuit comprises a first input terminal, a second input terminal, a third input terminal, and a control signal output terminal, wherein the first input terminal is configured to input the output voltage of the boost circuit, the second input terminal is configured to input the input power supply voltage of the boost circuit, the third input terminal is configured to input a voltage difference between the first end and the second end of the first resistor of the boost circuit, and the control signal output terminal is configured to output a control signal based on the output voltage of the boost circuit, the input power supply voltage of the boost circuit, and the voltage difference between the first end and the second end of the first resistor of the boost circuit, so as to control the conduction state and conduction time of the first switch and the second switch of the boost circuit. The control signal output by the control circuit can first make the first switch in an off state and the second switch in a conduction state, and then make the first switch in a conduction state and the second switch in an off state in each operation cycle of the boost circuit, so that the control signal output by the control circuit makes the inductor first in a discharge state and then in a charge state in each operation cycle of the boost circuit.

13. The control circuit of claim 12, wherein, The control circuit comprises: a calibration module, an input terminal of the calibration module is configured to input the output voltage of the boost circuit, and the calibration module is configured to output a reference current based on the output voltage of the boost circuit and a reference voltage set in the calibration module; a control module, a first input terminal of the control module is configured to input the reference current, a second input terminal of the control module is configured to input the output voltage of the boost circuit, a third input terminal of the control module is configured to input the input power supply voltage of the boost circuit, a fourth input terminal of the control module is configured to input the voltage difference between the first end and the second end of the first resistor of the boost circuit, and the control module is configured to output a duty cycle signal based on the reference current, the output voltage of the boost circuit, the input power supply voltage of the boost circuit, and the voltage difference between the first end and the second end of the first resistor of the boost circuit. A pulse width modulation module, a first input end of the pulse width modulation module inputs the duty cycle signal, and is configured to generate a corresponding pulse signal according to the duty cycle signal, and output the pulse signal to a control end of the first switch and a control end of the second switch, so as to control the conduction state and conduction time of the first switch and the second switch.

14. The control circuit of claim 13, wherein, Further comprising: A noise shaping module, an input end of the noise shaping module inputs the duty cycle signal, and is configured to perform noise shaping on the duty cycle signal, and output the noise-shaped duty cycle signal to the pulse width modulation module.

15. The control circuit of claim 13, wherein, Further comprising: A level shift module, an input end of the level shift module inputs the pulse signal, and is configured to convert the voltage of the pulse signal from a first voltage domain to a second voltage domain, and output the pulse signal converted from the first voltage domain to the second voltage domain to the control end of the first switch and the control end of the second switch, wherein the voltage in the second voltage domain is greater than the voltage in the first voltage domain.

16. The control circuit of claim 13, wherein, Further comprising: A current limiting module, an input end of the current limiting module inputs the current flowing through the inductor, and is configured to limit the current flowing through the inductor.

17. The control circuit of claim 13, wherein, Further comprising: A mode monitoring module, an input end of the mode monitoring module inputs the current flowing through the inductor, and is configured to monitor the current flowing through the inductor, and control the working mode of the inductor according to the current flowing through the inductor.

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