An intelligent correction system for phase shifting of capacitor motors

Abstract

The invention discloses an intelligent correction system for phase shifting of a capacitor motor, comprising a main winding, a secondary winding and a phase-shifting capacitor, and also comprising a power supply, a 1-sin (90°+α) negative pressure wave generating circuit, a sin (90°+α) reference wave generating circuit, a DC power supply circuit, a bridge comparison circuit and a capacitor charge-discharge switching circuit, wherein the power supply is a 220V sinusoidal AC power supply, and the bridge comparison circuit is used to compare the detection wave voltage signal with the sin (90°+α) secondary winding reference wave signal for potential, and output a discharge interruption signal of the phase-shifting capacitor to the capacitor charge-discharge switching circuit according to the comparison result, and the capacitor charge-discharge switching circuit connects the phase-shifting capacitor and the secondary winding through the power supply to form a charging circuit during the charging period of the phase-shifting capacitor; and avoids the power supply during the discharging period, and forms a discharge circuit through the phase-shifting capacitor and the secondary winding. The torque and efficiency of the capacitor motor of this scheme are significantly improved.

Description

Technical Field

[0001] The present invention relates to the technical field of motors, and in particular to an intelligent correction system for phase shifting of a capacitor motor. Background Art

[0002] The phase shifting of the existing capacitor motor is to use a phase-shifting capacitor connected in series with the secondary winding and then connected to the power supply. The power supply charges the phase-shifting capacitor through the secondary winding during the potential rising stage of the power supply, and during the potential falling stage of the power supply, the phase-shifting capacitor releases the stored charge back to the power supply through the secondary winding. The current obtains phase-shifting excitation when passing through the secondary winding.

[0003] However, in the existing capacitor motor, the voltage of the phase-shifting capacitor is completely connected in series with the power supply voltage before being loaded to the auxiliary winding. Although the phase of the zero potential point of the voltage loaded to both ends of the auxiliary winding is 90° ahead of the power supply phase, the superposition period of the discharge potential of the phase-shifting capacitor and the power supply potential is during the period when the power supply potential is 0° to 90°, which causes its peak potential to be 60° ahead of the power supply potential; and the superposition period of the discharge potential of the phase-shifting capacitor and the power supply potential is during the period when the power supply potential is 90° to 180°, which causes the amplitude of the voltage loaded at both ends of the auxiliary winding during this period to be seriously insufficient; resulting in extremely small lateral torque generated by the excitation of the auxiliary winding and low motor efficiency. Summary of the invention

[0004] In view of the above-mentioned deficiencies in the prior art, the technical problem to be solved by the present invention is: how to provide an intelligent correction system for capacitor motor phase shifting that can significantly improve the torque and efficiency of the capacitor motor.

[0005] In order to solve the above technical problems, the present invention adopts the following technical solutions:

[0006] An intelligent correction system for phase shifting of a capacitor motor, comprising a main winding, a secondary winding and a phase shifting capacitor, the intelligent correction system also comprising a power supply, a 1-sin (90°+α) negative pressure wave generating circuit, a sin (90°+α) reference wave generating circuit, a DC power supply circuit, a bridge comparison circuit and a capacitor charge and discharge switching circuit;

[0007] The power supply is a 220V sinusoidal AC power supply, and the power supply is used to generate a sinα negative pressure unidirectional wave voltage;

[0008] The sinα negative pressure unidirectional wave voltage generated by the power supply is rectified by the bridge rectifier T1 and stepped down by the resistor R10 to become a -30V sinα negative pressure unidirectional wave voltage, and the -30V sinα negative pressure unidirectional wave voltage is input into the 1-sin (90°+α) negative pressure wave generating circuit after being limited by the resistor R1, and the wave is attenuated into a -15V 1- sin (90°+α) unidirectional wave, and then conducted to the ground through the resistor R17 and the diode D12, and the 1-sin (90°+α) negative pressure wave generating circuit also inputs the synchronization signal of the phase-shift capacitor charging period to the capacitor charge and discharge switching circuit;

[0009] The DC power supply circuit extracts voltages at both ends of the phase-shifting capacitor, the secondary winding and the power supply, respectively, and steps down the voltage in advance into DC power of a first set value and a second set value, and the DC power of the first set value is output to the sin (90°+α) reference wave generating circuit, and the DC power of the second set value is output to the capacitor charge-discharge switching circuit;

[0010] The sin (90°+α) reference wave generating circuit is connected to the output end of the 1-sin (90°+α) negative pressure wave generating circuit through a resistor R17, and the end of the resistor R17 connected to the 1-sin (90°+α) negative pressure wave generating circuit is also connected to the anode of a diode D3, and the cathode of the diode D3 is grounded, and the end of the resistor R17 connected to the sin (90°+α) reference wave generating circuit is also connected to the cathode of a diode D12, and the anode of the diode D12 is grounded, and the sin (90°+α) reference wave generating circuit is connected to the DC output end of the DC power supply circuit that outputs a first set value through a resistor R21, and is used to generate a sin (90°+α) secondary phase reference wave signal voltage and input it into the bridge comparison circuit;

[0011] The bridge comparison circuit is used to compare the detection wave voltage signal with the secondary winding reference wave signal of sin (90°+α), and output the discharge interruption signal of the phase-shifting capacitor to the capacitor charge-discharge switching circuit according to the comparison result, and the rectifier bridge T3 obtains the 220V unidirectional detection wave voltage from both ends of the secondary winding, and is connected to ground after being connected in series with the resistor R23 and the resistor R18. The voltage at the connection point of the resistor R23 and the resistor R18 is input into the bridge comparison circuit as the detection wave voltage signal;

[0012] The capacitor charge and discharge switching circuit forms a charging circuit or a discharging circuit according to the capacitor discharge interruption signal of the bridge comparison circuit and the synchronization signal of the phase-shift capacitor charging period in the 1-sin (90°+α) negative pressure wave generating circuit, and the capacitor charge and discharge switching circuit connects the phase-shift capacitor and the secondary winding through the power supply to form a charging circuit during the phase-shift capacitor charging period; and avoids the power supply during the phase-shift capacitor discharging period, and forms a discharging circuit through the phase-shift capacitor and the secondary winding.

[0013] Preferably, the 1-sin (90°+α) negative pressure wave generating circuit includes a rectifier bridge T1, a resistor R1, a resistor R10, a resistor R14, a resistor R15, a resistor R19, a resistor R17, a diode D1, a diode D2, a diode D6, a diode D12, an NPN transistor BG1, an NPN transistor BG5, a PNP transistor BG6, a capacitor C1 and a capacitor C2, the two AC ends of the rectifier bridge T1 are connected to the power supply, the cathode end of the rectifier bridge T1 is grounded, the anode end of the rectifier bridge T1 is connected to one end of the resistor R10, the other end of the resistor R10 is connected to one end of the resistor R1, the other end of the resistor R1 is simultaneously connected to the emitter of the NPN transistor BG1 and the cathode of the diode D2, the anode of the diode D2 is connected to the cathode of the diode D1, and the anode of the diode D1 is simultaneously connected to the NPN transistor BG5 The base of the NPN transistor BG1 is connected to the emitter of the NPN transistor BG5 and one end of the capacitor C1 at the same time, and the other end of the capacitor C1 is grounded. The collector of the NPN transistor BG5 is connected to one end of the resistor R14 and one end of the capacitor C2 at the same time, and the other end of the capacitor C2 is connected to the other end of the resistor R14 and one end of the resistor R15 at the same time. The other end of the resistor R15 is connected to the base of the PNP transistor BG6, and the emitter of the PNP transistor BG6 is connected to one end of the resistor R19 and the anode of the diode D6 at the same time. The cathode of the diode D6 is grounded, one end of the resistor R17 is connected to the anode of the diode D1, and the other end of the resistor R17 is connected to the cathode of the diode D12, and the anode of the diode D12 is grounded.

[0014] Preferably, the sin (90°+α) reference wave generating circuit includes a rectifier bridge T2, a diode D3, a diode D15, a diode D16, a resistor R17, a resistor R21 and a resistor R22, the two AC ends of the rectifier bridge T2 are respectively connected to the two ends of the phase-shifting capacitor, the anode end of the rectifier bridge T2 is grounded, the cathode end of the rectifier bridge T2 is simultaneously connected to the cathode of the diode D15, the cathode of the diode D16 and one end of the resistor R22, the anode end of the diode D15 is connected to the cathode end of the rectifier bridge T3, the other end of the resistor R22 is connected to one end of the resistor R21, the other end of the resistor R21 is connected to one end of the resistor R17, the other end of the resistor R17 is connected to the anode end of the diode D3, and the cathode end of the diode D3 is grounded.

[0015] Preferably, the bridge comparison circuit includes a diode D9, a diode D10, a diode D11, a diode D13, a capacitor C3, a resistor R16 and a photoelectric coupler OC2, the anode of the diode D10 and the anode of the diode D11 are both connected to the connection point of the resistor R21 and the resistor R17, the cathode of the diode D11 is simultaneously connected to the anode of the photoelectric coupler OC2 and one end of the resistor R18 which is grounded, the cathode of the diode D10 is connected to the anode of the diode D9, the cathode of the diode D9 is connected to the cathode of the photoelectric coupler OC2 and then to one end of the resistor R16, the other end of the resistor R16 is connected to the anode of the diode D13, the cathode of the diode D13 is grounded, one end of the capacitor C3 is connected to the cathode of the diode D11, the other end of the capacitor C3 is connected to the cathode of the diode D12, and the collector of the photoelectric coupler OC2 is connected between the resistor R21 and the resistor R22.

[0016] Preferably, the intelligent correction system also includes a compensation power supply circuit, which includes a diode D14 and a resistor R24, the anode end of the diode D14 is grounded, the cathode end of the diode D14 is connected between the resistor R23 and the resistor R18, one end of the resistor R24 ​​is connected between the resistor R10 and the resistor R1, and the other end of the resistor R24 ​​is connected to the anode of the diode D13.

[0017] Preferably, the capacitor charge and discharge switching circuit includes a charging switch circuit and a discharging switch circuit, the charging switch circuit includes a rectifier bridge T4, a field effect transistor BT1, an NPN transistor BG3, a diode D8, a resistor R3, a resistor R4, a resistor R5, a resistor R6, a resistor R7, a resistor R8, a voltage regulator diode W2, a capacitor C5 and a photocoupler OC1, one AC end of the rectifier bridge T4 is connected to one end of the voltage, the other AC end is connected to one end of the phase-shifting capacitor, the other end of the phase-shifting capacitor is connected to one end of the secondary winding, the other end of the secondary winding is connected to the other end of the power supply, the anode end of the rectifier bridge T4 is grounded, the cathode end of the rectifier bridge T4 is connected to the drain of the field effect transistor BT1, the source of the field effect transistor BT1 is grounded through the resistor R5, the gate of the field effect transistor BT1 is connected to the collector of the NPN transistor BG3, the base of the NPN transistor BG3 is connected to the source of the field effect transistor BT1 through the resistor R6, and the The emitter of the NPN transistor BG3 is grounded, the emitter of the photoelectric coupler OC1 is connected to one end of the resistor R4 and the gate of the field effect transistor BT1 at the same time, the other end of the resistor R4 is grounded, the collector of the photoelectric coupler OC1 is connected to the cathode of the diode D8 and the positive electrode of the capacitor C5 at the same time through the resistor R9, the negative electrode of the capacitor C5 is grounded, the anode of the diode D8 is connected to one end of the resistor R7 and one end of the resistor R8 at the same time, the other end of the resistor R7 is connected to the drain of the field effect transistor BT1, the other end of the resistor R8 is grounded, the anode end of the Zener diode W2 is grounded, the cathode end of the Zener diode W2 is connected between the resistor R8 and the resistor R7, the anode of the photoelectric coupler OC1 is connected to the collector of the PNP transistor BG2 through the resistor R3, the base of the PNP transistor BG2 is connected to the collector of the NPN transistor BG1 through the resistor R2, and the cathode of the photoelectric coupler OC1 is grounded.

[0018] Preferably, the discharge switch circuit includes a rectifier bridge T5, a field effect transistor BT2, a PNP transistor BG7, an NPN transistor BG4, a diode D5, a resistor R11, a resistor R12, a resistor R13, a resistor R20, a resistor R25, a resistor R26, a voltage regulator diode W1 and a capacitor C4, one AC end of the rectifier bridge T5 is connected to one end of the phase-shift capacitor, the other AC end is connected to one end of the secondary winding connected to the power supply, the emitter of the NPN transistor BG4 is grounded, the base of the NPN transistor BG4 is simultaneously connected to the cathode of the diode D5 and one end of the resistor R12, the other end of the resistor R12 is connected to the emitter of the photocoupler OC2, and the collector of the NPN transistor BG4 is simultaneously connected to one end of the resistor R13, one end of the resistor R26 and the gate of the field effect transistor BT2. The other end of the resistor R26 is grounded, the other end of the resistor R13 is connected to the collector of the PNP transistor BG7, the emitter of the PNP transistor BG7 is simultaneously connected to the cathode of the Zener diode W1, one end of the resistor R20 and the positive electrode of the capacitor C4, the other end of the resistor R20 is connected between the resistor R21 and the resistor R22, the anode end of the Zener diode W1 is grounded, the negative electrode of the capacitor C4 is grounded, the base of the PNP transistor BG7 is connected to the collector of the NPN transistor BG5 through the resistor R25, the anode of the diode D5 is simultaneously connected to one end of the resistor R11 and the source of the field effect transistor BT2, the other end of the resistor R11 is grounded, the drain of the field effect transistor BT2 is connected to the cathode end of the rectifier bridge T5, and the anode end of the rectifier bridge T5 is grounded.

[0019] Compared with the prior art, the advantages of the present invention are:

[0020] 1. Since the power supply is first required to charge the phase-shifting capacitor during capacitor phase shifting, the existence of the secondary phase voltage and the power supply voltage in series is inevitable; and during the phase-shifting capacitor discharge period, the serious lack of voltage amplitude loaded at both ends of the secondary winding is completely due to the power supply voltage amplitude offsetting the secondary phase voltage amplitude. Therefore, this scheme sets up a capacitor charge-discharge switching circuit with extremely fast response speed between the power supply, the secondary winding and the phase-shifting capacitor; using the characteristics that in the unidirectional AC wave loading phase-shifting capacitor circuit, the phase-shifting capacitor is in a storage state during the rising period of the unidirectional AC wave potential, and the phase-shifting capacitor is in a discharge state during the falling period of the unidirectional AC wave potential. During the rising period of the power supply potential, the capacitor charge-discharge switching circuit controlled by the unidirectional AC wave connects the phase-shifting capacitor, the secondary winding and the power supply into a closed loop, allowing the power supply to charge the phase-shifting capacitor through the secondary winding; when the power supply potential drops, the capacitor charge-discharge switching circuit disconnects the power supply circuit and directly connects the capacitor and the secondary winding into a capacitor discharge circuit, thereby ensuring the voltage amplitude loaded at both ends of the secondary winding during the phase-shifting capacitor discharge period.

[0021] 2. During the phase-shift capacitor discharge period, the phase-shift capacitor will directly load the peak voltage to both ends of the secondary winding, causing the voltage loading amplitude to be extremely high during the secondary winding middle and low end potential loading period. Therefore, the present invention uses the rectifier bridge T1 to obtain a negative voltage unidirectional sine wave signal of sinα in the power supply, passes it through the resistor R1 to limit the current, and then uses the RC circuit to attenuate it to a negative voltage unidirectional wave of 1- sin (90° + α); and uses the positive voltage direct current to convert 1- The overall amplitude of the sin (90° + α) negative pressure unidirectional wave is increased by a peak voltage, turning it into a sin (90° + α) secondary phase voltage reference wave signal; the secondary phase voltage reference wave signal is then compared with the secondary phase voltage detection wave signal obtained at both ends of the secondary winding in a bridge comparison circuit. When the voltage amplitude of the secondary phase voltage detection wave signal is higher than the voltage amplitude of the secondary phase voltage reference wave signal, the bridge comparison circuit sends an interrupt signal to interrupt the capacitor charge and discharge switching circuit, causing the load voltage at both ends of the secondary winding to drop. When the voltage amplitude of the secondary phase voltage detection wave signal is lower than the voltage amplitude of the secondary phase voltage reference wave signal, the interrupt signal is terminated, allowing the voltage amplitude at both ends of the secondary winding to change with the voltage amplitude of the secondary phase voltage reference wave signal.

[0022] 3. Since the reference wave voltage and the detection wave voltage are synchronous unidirectional wave voltages, the current of the detection wave cannot drive the optocoupler to send an interruption signal near the zero potential of the voltage; therefore, the present invention uses a negative voltage unidirectional wave voltage of a power supply corresponding to the voltage values ​​of the reference wave and the detection wave to complementally supply power to the bridge balancing circuit. When the detection wave voltage is loaded at zero potential, the negative voltage unidirectional wave voltage of the power supply is loaded at the peak potential.

[0023] 4. During the period of 0° to 90° of the power supply voltage phase, due to the voltage loading at both ends of the secondary winding, it is necessary to load the power supply voltage in series from the residual discharge of the phase-shifting capacitor, and only during this period can there be sufficient voltage amplitude; and the discharge period of the phase-shifting capacitor is a rapid transition to the period of 90° to 210°, and the charging time is during the period of 30° to 90°. Under the condition of current limiting charging, the power supply has a serious shortage of power storage for the phase-shifting capacitor in each cycle. At this time, the system of the present invention is combined with the inventor's previous application with publication number CN111 A stator winding winding method in a wiring arrangement structure and working method of a capacitor motor stator winding of 245132A increases the peak limit of the auxiliary phase limited voltage amplitude at the 30° phase of the power supply voltage, and increases the phase-shifting capacitor storage by 1 / 3 within a limited range; and during the discharge period of the phase-shifting capacitor, the main winding distributed electrode can be moved 30° closer to the auxiliary winding, and the discharge load of the phase-shifting capacitor can be reduced by 1 / 3, thereby achieving the ultimate effect of the capacitor motor setting, and the torque and efficiency of the motor of the present invention are more significantly improved. BRIEF DESCRIPTION OF THE DRAWINGS

[0024] Figure 1 It is a system block diagram of the capacitor motor phase shift correction system of the present invention;

[0025] Figure 2 It is a specific circuit diagram of the capacitor motor phase shift correction system of the present invention. DETAILED DESCRIPTION

[0026] The present invention will be further described below in conjunction with the accompanying drawings and embodiments.

[0027] In order to make the purpose, technical scheme and advantages of the embodiments of the present invention clearer, the technical scheme in the embodiments of the present invention will be clearly and completely described below in conjunction with the drawings in the embodiments of the present invention. Obviously, the described embodiments are part of the embodiments of the present invention, not all of the embodiments. The components of the embodiments of the present invention generally described and shown in the drawings here can be arranged and designed in various different configurations. Therefore, the following detailed description of the embodiments of the present invention provided in the drawings is not intended to limit the scope of the claimed invention, but merely represents selected embodiments of the present invention. Based on the embodiments in the present invention, all other embodiments obtained by ordinary technicians in this field without making creative work belong to the scope of protection of the present invention.

[0028] It should be noted that similar numbers and letters represent similar items in the following drawings, so once an item is defined in one drawing, it does not need to be further defined and explained in the subsequent drawings. In the description of the present invention, it should be noted that the orientation or position relationship indicated by the terms "center", "upper", "lower", "left", "right", "vertical", "horizontal", "inside", "outside", etc. is based on the orientation or position relationship shown in the drawings, or the orientation or position relationship in which the invention product is usually placed when used, which is only for the convenience of describing the present invention and simplifying the description, rather than indicating or implying that the device or element referred to must have a specific orientation, be constructed and operated in a specific orientation, and therefore cannot be understood as a limitation of the present invention. In addition, the terms "first", "second", "third", etc. are only used to distinguish the description, and cannot be understood as indicating or implying relative importance. In addition, the terms "horizontal", "vertical", etc. do not mean that the components are absolutely horizontal or suspended, but can be slightly tilted. For example, "horizontal" only means that its direction is more horizontal than "vertical", and does not mean that the structure must be completely horizontal, but can be slightly tilted. In the description of the present invention, it is also necessary to explain that, unless otherwise clearly specified and limited, the terms "set", "install", "connect", and "connect" should be understood in a broad sense, for example, it can be a fixed connection, a detachable connection, or an integral connection; it can be a mechanical connection or an electrical connection; it can be a direct connection, or it can be indirectly connected through an intermediate medium, or it can be the internal communication of two elements. For ordinary technicians in this field, the specific meanings of the above terms in the present invention can be understood according to specific circumstances.

[0029] As attached Figure 1 and attached Figure 2 As shown, an intelligent correction system for phase shifting of a capacitor motor includes a main winding, an auxiliary winding and a phase shifting capacitor C. The intelligent correction system also includes a power supply, a 1-sin (90° + α) negative pressure wave generating circuit, a sin (90° + α) reference wave generating circuit, a DC power supply circuit, a bridge comparison circuit and a capacitor charge and discharge switching circuit;

[0030] The power supply is a 220V sinusoidal AC power supply, and the power supply is used to generate a sinα negative pressure unidirectional wave voltage;

[0031] The sinα negative pressure unidirectional wave voltage generated by the power supply is rectified by the bridge rectifier T1 and stepped down by the resistor R10 to become a -30V sinα negative pressure unidirectional wave voltage, and the -30V sinα negative pressure unidirectional wave voltage is input into the 1-sin (90°+α) negative pressure wave generating circuit after being limited by the resistor R1, and the wave is attenuated into a -15V 1- sin (90°+α) unidirectional wave, and then conducted to the ground through the resistor R17 and the diode D12, and the 1-sin (90°+α) negative pressure wave generating circuit also inputs the synchronization signal of the phase shift capacitor C during the charging period to the capacitor charge and discharge switching circuit;

[0032] The DC power supply circuit extracts voltages at both ends of the phase-shifting capacitor C, at both ends of the secondary winding and at both ends of the power supply, and steps down the voltage in advance into DC power of a first set value and DC power of a second set value, and the DC power of the first set value is output to the sin (90°+α) reference wave generating circuit, and the DC power of the second set value is output to the capacitor charge-discharge switching circuit;

[0033] The output end of the sin (90° + α) reference wave generating circuit and the 1-sin (90° + α) negative pressure wave generating circuit are connected through a resistor R17, and the end of the resistor R17 connected to the 1-sin (90° + α) negative pressure wave generating circuit is also connected to the anode of the diode D3, and the cathode of the diode D3 is grounded, and the end of the resistor R17 connected to the sin (90° + α) reference wave generating circuit is also connected to the cathode of the diode D12, and the anode of the diode D12 is grounded, and the sin (90° + α) reference wave generating circuit is connected to the DC output end of the DC power supply circuit that outputs the first set value through a resistor R21, which is used to generate a sin (90° + α) secondary phase reference wave signal voltage and input it into the bridge comparison circuit;

[0034] The bridge comparison circuit is used to compare the detection wave voltage signal with the secondary winding reference wave signal of sin (90°+α), and output the discharge interruption signal of the phase-shifting capacitor C to the capacitor charge-discharge switching circuit according to the comparison result, and the rectifier bridge T3 obtains the 220V unidirectional detection wave voltage from both ends of the secondary winding, and is connected to ground after being connected in series with the resistor R23 and the resistor R18. The voltage at the connection point of the resistor R23 and the resistor R18 is input into the bridge comparison circuit as the detection wave voltage signal;

[0035] The capacitor charge and discharge switching circuit forms a charging circuit or a discharging circuit according to the capacitor discharge interruption signal of the bridge comparison circuit and the synchronization signal of the phase-shift capacitor C charging period in the 1-sin (90°+α) negative pressure wave generating circuit, and the capacitor charge and discharge switching circuit connects the phase-shift capacitor C and the secondary winding through the power supply to form a charging circuit during the charging period of the phase-shift capacitor C; and avoids the power supply during the discharging period of the phase-shift capacitor C, and forms a discharging circuit through the phase-shift capacitor C and the secondary winding.

[0036] The present invention obtains a negative pressure unidirectional wave of sinα from a power source by a rectifier bridge T1, and after being stepped down by a resistor R10, becomes a unidirectional wave voltage of -30V; the -30V voltage is limited by a resistor R1, and then current is attenuated in a 1-sin (90°+α) negative pressure wave generating circuit, and is attenuated into a 1-sin (90°+α) unidirectional wave of -15V, and then passes through a load resistor R17, and is conducted to the ground through a diode D12. After the 42V direct current output from the direct current power supply circuit is grounded through a resistor R21, a resistor R17, and a diode D3, the direct current voltage at the connection point of the resistor R21 and the resistor R17 is 21V, and at the -15V 1- Under the attenuation effect of the sin (90°+α) unidirectional wave voltage on the 21V DC voltage, the voltage at the connection point of resistor R21 and resistor R17 becomes the secondary phase reference wave signal voltage of sin (90°+α); the 220V unidirectional detection wave voltage obtained by the rectifier bridge T3 from both ends of the secondary winding is connected in series to the ground through resistors R23 and R18, and a detection wave voltage matching the reference wave is obtained at the connection point of resistors R23 and R18.

[0037] The reference wave voltage and the detection wave voltage are connected to the bridge comparison circuit together, and the ground end of the bridge comparison circuit is grounded through the diode D13. Therefore, when the detection wave potential is higher than the reference wave potential, the bridge balance circuit outputs an interruption signal, interrupts the secondary winding current loading through the capacitor charge and discharge switching circuit, and reduces the loading voltage at both ends of the secondary winding; when the detection wave potential is lower than the reference wave potential, the bridge comparison circuit turns off the signal, and the secondary winding loop remains connected.

[0038] At the connection point of resistor R10 and resistor R1, resistor R24 ​​is also connected to the connection point of the ground terminal of the bridge comparison circuit and the diode D13, and a -15V power supply unidirectional wave voltage is applied to the ground terminal of the bridge comparison circuit; and diode D14 is connected to the ground at the detection wave input point. In this way, after passing through the bridge comparison circuit, the -15V power supply unidirectional wave current enters the ground through diode D14 in one way and enters the ground through diode D12 in the other way.

[0039] When the above-mentioned 1- sin (90° + α) negative pressure unidirectional wave is generated, a capacitor is used to attenuate the sinα unidirectional wave. Since the current direction of the capacitor is different during charging or discharging, the capacitor charging and discharging signals are taken out locally to control the capacitor charging and discharging switching circuit. When the alternating potential of the power supply rises, the phase-shifting capacitor C and the secondary winding are connected in series to the power supply through the capacitor charging and discharging switching circuit; when the alternating potential of the power supply drops, the phase-shifting capacitor C and the secondary winding are disconnected from the power supply through the capacitor charging and discharging switching circuit, and the phase-shifting capacitor C discharges directly to the secondary winding through the switching switch.

[0040] In addition, the system of the present invention can also be combined with the stator winding winding method in the stator winding arrangement structure of a capacitor motor stator winding and its working method with the publication number CN111245132A previously invented by the inventor. The winding structure is: first, the secondary winding is divided into parts in the stator core according to the arrangement method of the concentric winding, and the electrode division range cannot exceed 45° phase angle before and after; the main winding distribution is composed of two parts, one of which is distributed at the 90° phase angle position of the secondary phase electrode, and the two core slots adjacent to the secondary winding are pre-arranged. left out; the other part of the main winding is subdivided into shunt winding 1 and shunt winding 2, one electrode of shunt winding 1 is divided in the core slot outside the auxiliary phase 45°, and the other electrode is dispersed and overlapped on the auxiliary winding electrode on the -45° side of the auxiliary phase electrode; one of the electrodes of shunt winding 2 is divided in the core slot outside the auxiliary phase -45°, and the other electrode is dispersed and overlapped on the auxiliary winding electrode on the 45° side of the auxiliary phase electrode; the two shunt windings are then connected in parallel according to the winding direction of the main winding and then connected in series with the previous part of the main winding. After adopting the above-mentioned stator winding structure, during the period of 0° to 90° of the power supply potential, the direction of the electrode of the shunt winding 2 overlapping on the auxiliary winding is the same as the excitation direction of the auxiliary winding, and the strong impedance voltage can block the current of the shunt winding 2, and the excitation current distributed in the iron core slot outside the auxiliary phase -45° is blocked; while the direction of the electrode of the shunt winding 1 overlapping on the auxiliary winding is opposite to the excitation direction of the auxiliary winding, and the excitation energy of the auxiliary winding overlapping with it is induced and transmitted to the iron core slot outside the auxiliary phase 45° to strengthen the excitation; under the action of the pole shade, the auxiliary winding excitation electrode is offset by about 30° in the 45° direction, and the main winding excitation electrode is also rearranged to the 60° phase. When the power supply potential is between 90° and 180°, the direction of the electrode of the shunt winding 1 overlapping on the secondary winding is the same as the excitation direction of the secondary winding. The strong impedance voltage can block the current of the shunt winding 1, and the excitation current distributed in the core slot 45° outside the secondary phase is blocked; while the direction of the electrode of the shunt winding 2 overlapping on the secondary winding is opposite to the excitation direction of the secondary winding, and the excitation energy of the secondary winding overlapping with it is induced and transmitted to the core slot outside the secondary phase -45° to strengthen the excitation; under the action of the shaded pole, the excitation electrode of the secondary winding is offset by about 30° in the direction of -45°, and the excitation electrode of the main winding is also rearranged to the phase of 120°. As a result, during the charging period of the phase-shifting capacitor C, after the auxiliary winding excitation phase is shifted 30° toward 45°, the amplitude limit value of the auxiliary phase voltage at the 30° phase can be increased from 0.866 to 1, which can correspondingly increase the storage capacity of the phase-shifting capacitor C; and during the discharging period of the phase-shifting capacitor C, after the main winding excitation phase is shifted to 120°, 1 / 3 of the capacitor discharge excitation consumption can be reduced; the combination of the two can basically solve the serious shortage of storage capacity of the phase-shifting capacitor C.

[0041] After the system of the present invention is connected to the original capacitor motor, under the condition that the input current of the secondary winding is a sine wave, the amount of electricity that can be stored in the phase-shifting capacitor C can only meet the situation that when the power supply potential is between 90° and 135°, the phase-shifting capacitor C discharges and loads the secondary winding with a voltage with a sine wave amplitude; when the power supply potential is between 135° and 210°, the amount of electricity stored in the phase-shifting capacitor C under the current-limiting charging condition is seriously insufficient, resulting in the serious lack of amplitude of the loaded voltage at both ends of the secondary winding during the peak period; even so, the efficiency and torque of the motor are much improved compared with the original capacitor motor.

[0042] The invented system is combined with the stator winding method of the stator winding of a capacitor motor with a wiring structure and working method previously applied by the inventor with the publication number CN111245132A. During the period of 0° to 90° of the power supply voltage phase, due to the excitation of the auxiliary winding, when the main phase current in the bridge circuit is shunted, while the main winding distribution electrode is rearranged from 90° to 60°, its own electrode is also shifted from 0° to 30° after being shaded. In this way, when the power supply potential is 30°, the amplitude of the excitation current through the auxiliary winding can be increased from the original 0.866 to 1, which can accelerate the discharge of the residual electricity of the capacitor and charge it in reverse in time, so that the capacitor can store more electricity; during this period, the greater the current loaded by the auxiliary winding, the higher the voltage at both ends of the shunt winding of the motor of the present invention, resulting in a year-on-year decrease in the current loaded by the main winding, and the auxiliary winding is used to help the main winding bear the load to increase the storage capacity of the capacitor. During the period of 90° to 180° of the power supply voltage phase, when the auxiliary winding is excited and shunted to the main phase current in the bridge circuit, while rearranging the main winding distribution electrodes from 90° to 120°, its own electrodes are also shifted from 180° to 150° after being shaded. In this way, during the period of 90° to 120° of the power supply potential, the auxiliary winding controls the main winding to help its load under the condition of inputting a very small current, leaving a large amount of energy stored in the capacitor to be discharged during the peak current loading period of the auxiliary winding, which can solve the problem of insufficient voltage amplitude when the power supply potential is between 135° and 210°. The main winding helps the load of the auxiliary winding, and can also greatly reduce the auxiliary phase current, reduce the capacity configuration of the capacitor, reduce the current of the capacitor charge and discharge switching circuit of the present invention, reduce its heat generation, and can integrate the electronic circuit other than the phase-shifting capacitor in the wiring rack, thereby greatly reducing the manufacturing cost of accessories, and the installation is particularly convenient.

[0043] In addition, the system of the present invention adopts the original capacitor motor during the parallel excitation of the two-phase windings, and the two-phase electrode division distance is 90°; the two-phase winding of the three-phase motor during the parallel excitation of the two-phase windings, the two-phase electrode division distance is 60°. The system of the present invention adopts the stator winding winding method in the stator winding arrangement structure of the capacitor motor stator winding and its working method previously applied by the inventor with the publication number CN111245132A. During the parallel excitation of the two-phase windings of the motor, the two-phase electrode division distance is only 30°, which is better than the other two motors. It is particularly beneficial that it inputs current according to the fluctuation of the power supply voltage wave; unlike the DC variable frequency motor, the power supply can only load current to the inverter when the power supply potential is higher than the small amplitude of the voltage across the filter capacitor, causing great power pollution.

[0044] In this embodiment, the 1-sin (90°+α) negative pressure wave generating circuit includes a rectifier bridge T1, a resistor R1, a resistor R10, a resistor R14, a resistor R15, a resistor R19, a resistor R17, a diode D1, a diode D2, a diode D6, a diode D12, an NPN transistor BG1, an NPN transistor BG5, a PNP transistor BG6, a capacitor C1 and a capacitor C2, two AC ends of the rectifier bridge T1 are connected to a power supply, the cathode end of the rectifier bridge T1 is grounded, the anode end of the rectifier bridge T1 is connected to one end of the resistor R10, the other end of the resistor R10 is connected to one end of the resistor R1, the other end of the resistor R1 is simultaneously connected to the emitter of the NPN transistor BG1 and the cathode of the diode D2, the anode of the diode D2 is connected to the cathode of the diode D1, and the anode of the diode D1 is simultaneously connected to The base of NPN transistor BG5 and the collector of PNP transistor BG6, the base of NPN transistor BG1 are connected to the emitter of NPN transistor BG5 and one end of capacitor C1 at the same time, the other end of capacitor C1 is grounded, the collector of NPN transistor BG5 is connected to one end of resistor R14 and one end of capacitor C2 at the same time, the other end of capacitor C2 is connected to the other end of resistor R14 and one end of resistor R15 at the same time, the other end of resistor R15 is connected to the base of PNP transistor BG6, the emitter of PNP transistor BG6 is connected to one end of resistor R19 and the anode of diode D6 at the same time, the cathode of diode D6 is grounded, one end of resistor R17 is connected to the anode of diode D1, the other end of resistor R17 is connected to the cathode of diode D12, and the anode of diode D12 is grounded.

[0045] In this way, the negative voltage unidirectional wave output by the power supply through the rectifier bridge T1 is stepped down to a -30V unidirectional wave voltage through resistor R10, and then passes through resistor R1, diode D2, diode D1, resistor R17 and diode D12 in sequence to form a current loop. Under the condition that resistor R1 = resistor R17, the voltage at point E at the anode end of diode D1 is a -15V unidirectional wave voltage, and the current is limited by resistor R1. Therefore, when the negative voltage potential at point E rises, capacitor C1 shunts current to point E through the base and emitter of NPN transistor BG1, reducing the voltage amplitude at point E; when the negative voltage potential at point E is in a decreasing period, the stored electricity in capacitor C1 is released through the base and emitter of NPN transistor BG5, the collector and emitter of NPN transistor BG5 are turned on, the base current of PNP transistor BG6 is turned on through resistor R15, resistor R14, capacitor C2 and NPN transistor BG5, and the current from the collector to the emitter of PNP transistor BG6 attenuates the negative voltage potential at point E during this period.

[0046] During the potential decay at point E of capacitor C1 during discharge, the current through PNP transistor BG6 needs to decay the stored electricity of capacitor C1 and the current from resistor R1 at the same time; therefore, it uses capacitor C2 to accelerate the decay of its peak period and slow down the decay of the trough period, decaying the negative pressure wave after sinα to a negative pressure wave of 1- sin (90° + α). Diodes D1 and D2 are set to offset the PN junction voltage between the base and emitter of NPN transistors BG1 and BG5. If there is no voltage difference between the emitter of NPN transistor BG1 and the base of NPN transistor BG5, capacitor C1 cannot load current to NPN transistor BG5 in time when switching from charging to discharging. Resistor R19 and diode D6 form a 0.55V power supply circuit. Resistor R19 obtains power from a 5V power supply, and the voltage is reduced to 0.55V through the PN junction of diode D6.

[0047] In this embodiment, the sin (90° + α) reference wave generating circuit includes a rectifier bridge T2, a diode D3, a diode D15, a diode D16, a resistor R17, a resistor R21 and a resistor R22. The two AC ends of the rectifier bridge T2 are respectively connected to the two ends of the phase-shifting capacitor C, the anode end of the rectifier bridge T2 is grounded, the cathode end of the rectifier bridge T2 is simultaneously connected to the cathode of the diode D15, the cathode of the diode D16 and one end of the resistor R22, the anode end of the diode D15 is connected to the cathode end of the rectifier bridge T3, the other end of the resistor R22 is connected to one end of the resistor R21, the other end of the resistor R21 is connected to one end of the resistor R17, the other end of the resistor R17 is connected to the anode end of the diode D3, and the cathode end of the diode D3 is grounded.

[0048] In this way, the rectifier bridge T2 collects the power at both ends of the phase-shifting capacitor C, the diode D15 collects the auxiliary phase power, and the diode D16 collects the main phase power, which are then combined and stepped down to a 42V DC power supply through the resistor R22; under the condition that the resistor R21=resistor R17, the 42V DC power is stepped down and limited by the resistor R21, and then conducted to the ground by the resistor R17 and the diode D3, so that the DC voltage at the connection point between the resistor R21 and the resistor R17 becomes 21V; because the diode D3 cannot conduct the negative voltage to the ground, the -15V unidirectional wave coming from the anode of the diode D1 attenuates the DC voltage at the connection point between the resistor R21 and the resistor R17 through the resistor R17, and under the condition that the DC voltage at the connection point between the resistor R21 and the resistor R17 is equal to the -15V unidirectional wave peak voltage, the voltage at the connection point between the resistor R21 and the resistor R17 becomes a 15V sin (90°+α) unidirectional wave voltage.

[0049] In this embodiment, the bridge comparison circuit includes a diode D9, a diode D10, a diode D11, a diode D13, a capacitor C3, a resistor R16 and a photocoupler OC2. The anode of the diode D10 and the anode of the diode D11 are both connected to the connection point of the resistor R21 and the resistor R17. The cathode of the diode D11 is simultaneously connected to the anode of the photocoupler OC2 and one end of the resistor R18 which is grounded. The cathode of the diode D10 is connected to the anode of the diode D9. The cathode of the diode D9 is connected to the cathode of the photocoupler OC2 and then to one end of the resistor R16. The other end of the resistor R16 is connected to the anode of the diode D13. The cathode of the diode D13 is grounded. One end of the capacitor C3 is connected to the cathode of the diode D11. The other end of the capacitor C3 is connected to the cathode of the diode D12. The collector of the photocoupler OC2 is connected between the resistor R21 and the resistor R22.

[0050] In this way, the current at points A and B to the ground shows three current loops. The first current loop goes from point A through diode D10 and diode D9 to point F and then through resistor R16 and diode D13 to the ground; the second current loop goes from point A through diode D11 and photocoupler OC2 to point F and then through resistor R16 and diode D13 to the ground; the third current loop goes from point B through photocoupler OC2 to point F and then through resistor R16 and diode D13 to the ground. However, the voltage drop from point A to point F through diode D10 and diode D9 is the PN junction voltage drop of two diodes, that is, 0.5V+0.5V=1.1V, and the voltage drop from point A to point F through diode D11 and photocoupler OC2 is the PN junction voltage drop of one diode and the PN junction voltage drop of a photocoupler diode, that is, 0.5V+V=1.5V; Obviously, the current at point A can only pass through diode D10 and diode D9 to point F and then pass through resistor R16 and diode D13 to enter the ground, and the current from point A to point F through diode D11 and photocoupler OC2 and then pass through resistor R16 and diode D13 to enter the ground does not exist. Then, the current from point B to point F through photocoupler OC2 and then pass through resistor R16 and diode D13 to enter the ground must also exist when the potential at point B is 1V higher than the potential at point F. Therefore, the potential at point B can only operate below the equilibrium point of the input at point A. Once it exceeds the equilibrium point, the optocoupler will immediately send an interrupt signal.

[0051] Since the reference wave signal and the detection wave signal obtained above are both voltage signals and have no current supply capability, when the optocoupler loads current, part of the original current channel to the ground at point A is occupied by point B, the potential at point A will rise, and the potential at point B will drop synchronously. Therefore, a capacitor C3 is connected between points A and B, and the characteristic that the internal current of the capacitor leads the voltage is utilized to drive the optocoupler OC2 by the capacitor discharge current. In addition, when the optocoupler OC2 is turned on, the ground loop of resistor R12 can pull down the rising potential of point A year on year, and the potential balance between points A and B will not be broken.

[0052] In this embodiment, the intelligent correction system also includes a compensation power supply circuit, which includes a diode D14 and a resistor R24. The anode end of the diode D14 is grounded, the cathode end of the diode D14 is connected between the resistor R23 and the resistor R18, one end of the resistor R24 ​​is connected between the resistor R10 and the resistor R1, and the other end of the resistor R24 ​​is connected to the anode of the diode D13.

[0053] In this way, after the -30V unidirectional wave voltage is reduced to -15V by resistor R24, it enters the zero potential end of the bridge comparison circuit to apply negative voltage to the bridge balance circuit. After the current passes through the bridge comparison circuit, point A is conducted to the ground by diode D12, and point B is conducted to the ground by diode D14. When the potentials of points A and B are at the peak potential, the -15V unidirectional wave is at zero potential; when the potentials of points A and B are at zero potential, the -15V unidirectional wave is at the peak potential. In this way, when the detection wave is close to zero potential, it can effectively drive the photocoupler OC2 to operate.

[0054] In this embodiment, the capacitor charge and discharge switching circuit includes a charging switch circuit and a discharging switch circuit. The charging switch circuit includes a rectifier bridge T4, a field effect transistor BT1, an NPN transistor BG3, a diode D8, a resistor R3, a resistor R4, a resistor R5, a resistor R6, a resistor R7, a resistor R8, a voltage regulator diode W2, a capacitor C5 and a photocoupler OC1. One AC end of the rectifier bridge T4 is connected to one end of the voltage, and the other AC end is connected to one end of the phase-shifting capacitor C. The other end of the phase-shifting capacitor C is connected to one end of the secondary winding, and the other end of the secondary winding is connected to the other end of the power supply. The anode end of the rectifier bridge T4 is grounded, the cathode end of the rectifier bridge T4 is connected to the drain of the field effect transistor BT1, the source of the field effect transistor BT1 is grounded through the resistor R5, the gate of the field effect transistor BT1 is connected to the collector of the NPN transistor BG3, and the base of the NPN transistor BG3 is connected to the field effect transistor BT1 through the resistor R6. The source of the transistor BG3 is connected, the emitter of the NPN transistor BG3 is grounded, the emitter of the photocoupler OC1 is connected to one end of the resistor R4 and the gate of the field effect transistor BT1 at the same time, the other end of the resistor R4 is grounded, the collector of the photocoupler OC1 is connected to the cathode of the diode D8 and the positive electrode of the capacitor C5 at the same time through the resistor R9, the negative electrode of the capacitor C5 is grounded, the anode of the diode D8 is connected to one end of the resistor R7 and one end of the resistor R8 at the same time, the other end of the resistor R7 is connected to the drain of the field effect transistor BT1, the other end of the resistor R8 is grounded, the anode terminal of the Zener diode W2 is grounded, the cathode terminal of the Zener diode W2 is connected between the resistor R8 and the resistor R7, the anode of the photocoupler OC1 is connected to the collector of the PNP transistor BG2 through the resistor R3, the base of the PNP transistor BG2 is connected to the collector of the NPN transistor BG1 through the resistor R2, and the cathode of the photocoupler OC1 is grounded.

[0055] In this way, the two AC ends of the rectifier bridge T4, the phase-shifting capacitor C, the secondary winding and the power supply constitute an alternating charging circuit for the phase-shifting capacitor C, and the drain, source and resistor R5 of the field effect transistor BT1 constitute the DC circuit of the rectifier bridge T4; when the drain and source ends of the field effect transistor BT1 generate current in one direction, the two AC ends of the rectifier bridge T4 will generate current in the direction of the power supply voltage, thus turning the unidirectional switch into a bidirectional switch. The diode D8, the resistor R7, the resistor R8, the voltage regulator diode W2 and the capacitor C5 constitute a 5V isolated power supply that drives the gate of the field effect transistor BT1; when the field effect transistor BT1 is turned off, the resistor R7, the resistor R8 and the voltage regulator diode W2 obtain the 5V power supply from the drain end of the field effect transistor BT1 and store the capacitor C5 through the diode D8, and output it when the field effect transistor BT1 is turned on. Resistors R5, R6 and NPN transistor BG3 constitute a protection circuit for field effect transistor BT1. When the voltage at the connection point between the source terminal of field effect transistor BT1 and resistor R5 is higher than 0.65V, NPN transistor BG3 is turned on to turn off the current of field effect transistor BT1. Resistor R4 is the lower bias resistor of field effect transistor BT1. When the gate terminal voltage of field effect transistor BT1 is turned off, resistor R4 can discharge the gate charge of field effect transistor BT1. Optocoupler OC1 and Zener diode W2 constitute a control signal input gate circuit for field effect transistor BT1. Optocoupler OC1 will only be driven when the input voltage is 4.3V relative to ground.

[0056] In this embodiment, the discharge switch circuit includes a rectifier bridge T5, a field effect transistor BT2, a PNP transistor BG7, an NPN transistor BG4, a diode D5, a resistor R11, a resistor R12, a resistor R13, a resistor R20, a resistor R25, a resistor R26, a voltage regulator diode W1 and a capacitor C4. One AC end of the rectifier bridge T5 is connected to one end of the phase-shifting capacitor, and the other AC end is connected to one end of the secondary winding connected to the power supply. The emitter of the NPN transistor BG4 is grounded, and the base of the NPN transistor BG4 is simultaneously connected to the cathode of the diode D5 and one end of the resistor R12. The other end of the resistor R12 is connected to the emitter of the photocoupler OC2, and the collector of the NPN transistor BG4 is simultaneously connected to one end of the resistor R13, one end of the resistor R26 and the field effect The gate of the field effect transistor BT2 is connected, the other end of the resistor R26 is grounded, the other end of the resistor R13 is connected to the collector of the PNP transistor BG7, the emitter of the PNP transistor BG7 is connected to the cathode of the Zener diode W1, one end of the resistor R20 and the positive electrode of the capacitor C4 at the same time, the other end of the resistor R20 is connected between the resistor R21 and the resistor R22, the anode end of the Zener diode W1 is grounded, the negative electrode of the capacitor C4 is grounded, the base of the PNP transistor BG7 is connected to the collector of the NPN transistor BG5 through the resistor R25, the anode of the diode D5 is connected to one end of the resistor R11 and the source of the field effect transistor BT2 at the same time, the other end of the resistor R11 is grounded, the drain of the field effect transistor BT2 is connected to the cathode end of the rectifier bridge T5, and the anode end of the rectifier bridge T5 is grounded.

[0057] In this way, the two AC ends of the rectifier bridge T5, the phase-shift capacitor C and the secondary winding constitute the alternating discharge circuit of the phase-shift capacitor C, and the drain and source ends of the field effect tube BT2 and the resistor R11 constitute the DC circuit of the rectifier bridge T5; when the drain and source of the field effect tube BT2 generate current in one direction, the two AC ends of the rectifier bridge T5 will generate current in the discharge direction of the phase-shift capacitor C, thus turning the unidirectional switch into a bidirectional switch. The diode D6, the resistor R19, the resistor R20, the voltage-stabilizing diode W1 and the capacitor C4 constitute a 5V power supply to drive the emitter of the PNP transistor BG7; the DC power obtained by the resistor R20 from the 42V DC power supply is attenuated to the ground by the resistor R19 and the diode D6, and the voltage-stabilizing diode W1 and the capacitor C4 are used for voltage stabilization and filtering to obtain a 5V DC power supply to drive the emitter of the PNP transistor BG7. Diode D5, resistor R11 and NPN transistor BG4 form a protection circuit for field effect transistor BT2. When the voltage at the connection point between the source terminal of field effect transistor BT2 and resistor R11 is higher than 0.95V, NPN transistor BG4 is turned on and the current of field effect transistor BT2 is turned off. Resistor R12 is the interrupt signal input resistor of field effect transistor BT2. When the photocoupler OC2 outputs the interrupt signal, the current passes through resistor R12 to turn on NPN transistor BG4, and the current of field effect transistor BT2 is disconnected. Field effect transistor BT3 forms a control signal input gate circuit for field effect transistor BT2. When the input voltage to ground reaches 3.3V, field effect transistor BT3 is turned on and the current of field effect transistor BT2 is completely cut off.

[0058] PNP transistor BG2 and resistor R2 are the inverting circuit of the switching signal; the emitter of PNP transistor BG2 is connected to a 5V DC power supply, the base of PNP transistor BG2 is connected to one end of resistor R2, and the other end of resistor R2 is connected to the collector of NPN transistor BG1; the switching signal output from the collector of NPN transistor BG1 is input to the base of PNP transistor BG2 after current limiting by resistor R2, turning on the current of PNP transistor BG2, and when the collector voltage of PNP transistor BG2 rises to 3.3V, the current of field effect transistor BT2 is completely cut off; when the collector voltage of PNP transistor BG2 continues to rise to 4.3V, field effect transistor BT1 is turned on. Since the charging and discharging time of capacitor C1 is completely synchronized with the charging and discharging time of phase-shift capacitor C, it is natural that the charging and discharging signal of capacitor C1 controls the charging and discharging switching of phase-shift capacitor C.

[0059] Compared with the prior art, the present invention requires a power supply to charge the phase-shifting capacitor C first during capacitor phase shifting, so the existence of a series connection between the secondary phase voltage and the power supply voltage is inevitable; and during the discharge period of the phase-shifting capacitor C, the serious deficiency of the voltage amplitude loaded at both ends of the secondary winding is entirely due to the power supply voltage amplitude offsetting the secondary phase voltage amplitude. Therefore, this scheme sets up a capacitor charge and discharge switching circuit with extremely fast response speed between the power supply, the secondary winding and the phase-shifting capacitor C; utilizing the characteristics that in the circuit of the unidirectional AC wave loading the phase-shifting capacitor C, when the potential of the unidirectional AC wave is rising, the phase-shifting capacitor C is in a storage state, and when the potential of the unidirectional AC wave is falling, the phase-shifting capacitor C is in a discharge state. During the period of rising power supply potential, the capacitor charge and discharge switching circuit controlled by the unidirectional AC wave connects the phase-shifting capacitor C, the secondary winding and the power supply into a closed loop, so that the power supply charges the phase-shifting capacitor C through the secondary winding; when the power supply potential drops, the capacitor charge and discharge switching circuit disconnects the power supply circuit, and directly connects the capacitor and the secondary winding into a capacitor discharge circuit, so as to ensure the voltage amplitude loaded at both ends of the secondary winding during the discharge of the phase-shifting capacitor C.

[0060] At the same time, during the phase-shift capacitor C discharge period, the phase-shift capacitor C will directly load the peak voltage to both ends of the secondary winding, causing the voltage loading amplitude to be extremely high during the secondary winding's mid- and low-end potential loading period. Therefore, the present invention uses the rectifier bridge T1 to obtain a sinα negative voltage unidirectional sine wave signal in the power supply, limits the current through the resistor R1, and then uses the RC circuit to attenuate it to a 1- sin (90° + α) negative voltage unidirectional wave; and uses the positive voltage direct current to convert the 1- The overall amplitude of the sin (90° + α) negative pressure unidirectional wave is increased by a peak voltage, turning it into a sin (90° + α) secondary phase voltage reference wave signal; the secondary phase voltage reference wave signal is then compared with the secondary phase voltage detection wave signal obtained at both ends of the secondary winding in a bridge comparison circuit. When the voltage amplitude of the secondary phase voltage detection wave signal is higher than the voltage amplitude of the secondary phase voltage reference wave signal, the bridge comparison circuit sends an interrupt signal to interrupt the capacitor charge and discharge switching circuit, causing the load voltage at both ends of the secondary winding to drop. When the voltage amplitude of the secondary phase voltage detection wave signal is lower than the voltage amplitude of the secondary phase voltage reference wave signal, the interrupt signal is terminated, allowing the voltage amplitude at both ends of the secondary winding to change with the voltage amplitude of the secondary phase voltage reference wave signal.

[0061] In addition, since the reference wave voltage and the detection wave voltage are synchronized unidirectional wave voltages, the current of the detection wave cannot drive the optocoupler to send an interruption signal near the zero potential of the voltage; therefore, the present invention uses a negative voltage unidirectional wave voltage of a power supply corresponding to the voltage value of the reference wave and the detection wave to complementally supply power to the bridge balancing circuit. When the detection wave voltage is loaded at zero potential, the negative voltage unidirectional wave voltage of the power supply is loaded at the peak potential.

[0062] Furthermore, during the period of 0° to 90° of the power supply voltage phase, due to the voltage loading at both ends of the secondary winding, it is necessary to load the power supply voltage in series from the residual discharge of the phase-shifting capacitor C, and only during this period is there sufficient voltage amplitude; and the discharge period of the phase-shifting capacitor C is a rapid transition to the period of 90° to 210°, and the charging time is during the period of 30° to 90°. Under the condition of current limiting charging, the power supply has a serious shortage of power storage for the phase-shifting capacitor C in each cycle. At this time, the system of the present invention is combined with the inventor's previous application with publication number CN11 A stator winding winding method in a wiring arrangement structure and working method of a capacitor motor stator winding of 1245132A increases the peak limit of the auxiliary phase limited voltage amplitude at the 30° phase of the power supply voltage, and increases the phase-shifting capacitor storage by 1 / 3 within a limited range; and during the discharge period of the phase-shifting capacitor C, the main winding distribution electrode can be moved 30° closer to the auxiliary winding, and the discharge load of the phase-shifting capacitor C can be reduced by 1 / 3, thereby achieving the ultimate effect of the capacitor motor setting, and the torque and efficiency of the motor of the present invention are more significantly improved.

[0063] Finally, it should be noted that the above embodiments are only used to illustrate the technical solution of the present invention rather than to limit the technical solution. Those skilled in the art should understand that those modifications or equivalent substitutions of the technical solution of the present invention that do not depart from the purpose and scope of the technical solution should be included in the scope of the claims of the present invention.

Claims

1. An intelligent correction system for phase shifting of a capacitor motor, comprising a main winding, a secondary winding and a phase shifting capacitor, characterized in that: The intelligent correction system also includes a power supply, a 1-sin (90° + α) negative pressure wave generating circuit, a sin (90° + α) reference wave generating circuit, a DC power supply circuit, a bridge comparison circuit and a capacitor charge and discharge switching circuit; The power supply is a 220V sinusoidal AC power supply, and the power supply is used to generate a sinα negative pressure unidirectional wave voltage; The sinα negative pressure unidirectional wave voltage generated by the power supply is rectified by the bridge rectifier T1 and stepped down by the resistor R10 to become a -30V sinα negative pressure unidirectional wave voltage, and the -30V sinα negative pressure unidirectional wave voltage is input into the 1-sin (90°+α) negative pressure wave generating circuit after being limited by the resistor R1, and the wave is attenuated into a -15V 1- sin (90°+α) unidirectional wave, and then conducted to the ground through the resistor R17 and the diode D12, and the 1-sin (90°+α) negative pressure wave generating circuit also inputs the synchronization signal of the phase-shift capacitor charging period to the capacitor charge and discharge switching circuit; The DC power supply circuit extracts voltages at both ends of the phase-shifting capacitor, the secondary winding and the power supply, respectively, and steps down the voltage in advance into DC power of a first set value and a second set value, and the DC power of the first set value is output to the sin (90°+α) reference wave generating circuit, and the DC power of the second set value is output to the capacitor charge-discharge switching circuit; The sin (90°+α) reference wave generating circuit is connected to the output end of the 1-sin (90°+α) negative pressure wave generating circuit through a resistor R17, and the end of the resistor R17 connected to the 1-sin (90°+α) negative pressure wave generating circuit is also connected to the anode of a diode D3, and the cathode of the diode D3 is grounded, and the end of the resistor R17 connected to the sin (90°+α) reference wave generating circuit is also connected to the cathode of a diode D12, and the anode of the diode D12 is grounded, and the sin (90°+α) reference wave generating circuit is connected to the DC output end of the DC power supply circuit that outputs a first set value through a resistor R21, and is used to generate a sin (90°+α) secondary phase reference wave signal voltage and input it into the bridge comparison circuit; The bridge comparison circuit is used to compare the detection wave voltage signal with the secondary winding reference wave signal of sin (90°+α), and output the discharge interruption signal of the phase-shifting capacitor to the capacitor charge-discharge switching circuit according to the comparison result, and the rectifier bridge T3 obtains the 220V unidirectional detection wave voltage from both ends of the secondary winding, and is connected to ground after being connected in series with the resistor R23 and the resistor R18. The voltage at the connection point of the resistor R23 and the resistor R18 is input into the bridge comparison circuit as the detection wave voltage signal; The capacitor charge and discharge switching circuit forms a charging circuit or a discharging circuit according to the capacitor discharge interruption signal of the bridge comparison circuit and the synchronization signal of the phase-shift capacitor charging period in the 1-sin (90°+α) negative pressure wave generating circuit, and the capacitor charge and discharge switching circuit connects the phase-shift capacitor and the secondary winding through the power supply to form a charging circuit during the phase-shift capacitor charging period; and avoids the power supply during the phase-shift capacitor discharging period, and forms a discharging circuit through the phase-shift capacitor and the secondary winding.

2. The intelligent correction system for capacitor motor phase shift according to claim 1 is characterized in that: The 1-sin (90°+α) negative pressure wave generating circuit includes a rectifier bridge T1, a resistor R1, a resistor R10, a resistor R14, a resistor R15, a resistor R19, a resistor R17, a diode D1, a diode D2, a diode D6, a diode D12, an NPN transistor BG1, an NPN transistor BG5, a PNP transistor BG6, a capacitor C1 and a capacitor C2, two AC ends of the rectifier bridge T1 are connected to the power supply, the cathode end of the rectifier bridge T1 is grounded, the anode end of the rectifier bridge T1 is connected to one end of the resistor R10, the other end of the resistor R10 is connected to one end of the resistor R1, the other end of the resistor R1 is simultaneously connected to the emitter of the NPN transistor BG1 and the cathode of the diode D2, the anode of the diode D2 is connected to the cathode of the diode D1, and the anode of the diode D1 is simultaneously connected to the base of the NPN transistor BG5. The base of the NPN transistor BG1 is connected to the emitter of the NPN transistor BG5 and one end of the capacitor C1 at the same time, and the other end of the capacitor C1 is grounded. The collector of the NPN transistor BG5 is connected to one end of the resistor R14 and one end of the capacitor C2 at the same time, and the other end of the capacitor C2 is connected to the other end of the resistor R14 and one end of the resistor R15 at the same time. The other end of the resistor R15 is connected to the base of the PNP transistor BG6, the emitter of the PNP transistor BG6 is connected to one end of the resistor R19 and the anode of the diode D6 at the same time, and the cathode of the diode D6 is grounded. One end of the resistor R17 is connected to the anode of the diode D1, and the other end of the resistor R17 is connected to the cathode of the diode D12, and the anode of the diode D12 is grounded.

3. The intelligent correction system for capacitor motor phase shift according to claim 2, characterized in that: The sin (90°+α) reference wave generating circuit includes a rectifier bridge T2, a diode D3, a diode D15, a diode D16, a resistor R17, a resistor R21 and a resistor R22. The two AC ends of the rectifier bridge T2 are respectively connected to the two ends of the phase-shifting capacitor, the anode end of the rectifier bridge T2 is grounded, the cathode end of the rectifier bridge T2 is simultaneously connected to the cathode of the diode D15, the cathode of the diode D16 and one end of the resistor R22, the anode end of the diode D15 is connected to the cathode end of the rectifier bridge T3, the other end of the resistor R22 is connected to one end of the resistor R21, the other end of the resistor R21 is connected to one end of the resistor R17, the other end of the resistor R17 is connected to the anode end of the diode D3, and the cathode end of the diode D3 is grounded.

4. The intelligent correction system for capacitor motor phase shift according to claim 3 is characterized in that: The bridge comparison circuit includes a diode D9, a diode D10, a diode D11, a diode D13, a capacitor C3, a resistor R16 and a photoelectric coupler OC2. The anode of the diode D10 and the anode of the diode D11 are both connected to the connection point of the resistor R21 and the resistor R17. The cathode of the diode D11 is simultaneously connected to the anode of the photoelectric coupler OC2 and one end of the resistor R18 that is grounded. The cathode of the diode D10 is connected to the anode of the diode D9. The cathode of the diode D9 is connected to the cathode of the photoelectric coupler OC2 and then to one end of the resistor R16. The other end of the resistor R16 is connected to the anode of the diode D13. The cathode of the diode D13 is grounded. One end of the capacitor C3 is connected to the cathode of the diode D11. The other end of the capacitor C3 is connected to the cathode of the diode D12. The collector of the photoelectric coupler OC2 is connected between the resistor R21 and the resistor R22.

5. The intelligent correction system for capacitor motor phase shift according to claim 4 is characterized in that: The intelligent correction system also includes a compensation power supply circuit, which includes a diode D14 and a resistor R24. The anode end of the diode D14 is grounded, the cathode end of the diode D14 is connected between the resistor R23 and the resistor R18, one end of the resistor R24 ​​is connected between the resistor R10 and the resistor R1, and the other end of the resistor R24 ​​is connected to the anode of the diode D13.

6. The intelligent correction system for capacitor motor phase shift according to claim 5, characterized in that: The capacitor charge and discharge switching circuit includes a charging switch circuit and a discharging switch circuit. The charging switch circuit includes a rectifier bridge T4, a field effect tube BT1, an NPN transistor BG3, a diode D8, a resistor R3, a resistor R4, a resistor R5, a resistor R6, a resistor R7, a resistor R8, a voltage regulator diode W2, a capacitor C5 and a photoelectric coupler OC1. One AC end of the rectifier bridge T4 is connected to one end of the voltage, and the other AC end is connected to one end of the phase-shifting capacitor. The other end of the phase-shifting capacitor is connected to one end of the secondary winding, and the other end of the secondary winding is connected to the other end of the power supply. The anode end of the rectifier bridge T4 is grounded, the cathode end of the rectifier bridge T4 is connected to the drain of the field effect tube BT1, the source of the field effect tube BT1 is grounded through the resistor R5, the gate of the field effect tube BT1 is connected to the collector of the NPN transistor BG3, the base of the NPN transistor BG3 is connected to the source of the field effect tube BT1 through the resistor R6, and the N The emitter of the PN transistor BG3 is grounded, the emitter of the photoelectric coupler OC1 is connected to one end of the resistor R4 and the gate of the field effect transistor BT1 at the same time, the other end of the resistor R4 is grounded, the collector of the photoelectric coupler OC1 is connected to the cathode of the diode D8 and the positive electrode of the capacitor C5 at the same time through the resistor R9, the negative electrode of the capacitor C5 is grounded, the anode of the diode D8 is connected to one end of the resistor R7 and one end of the resistor R8 at the same time, the other end of the resistor R7 is connected to the drain of the field effect transistor BT1, the other end of the resistor R8 is grounded, the anode end of the Zener diode W2 is grounded, the cathode end of the Zener diode W2 is connected between the resistor R8 and the resistor R7, the anode of the photoelectric coupler OC1 is connected to the collector of the PNP transistor BG2 through the resistor R3, the base of the PNP transistor BG2 is connected to the collector of the NPN transistor BG1 through the resistor R2, and the cathode of the photoelectric coupler OC1 is grounded.

7. The intelligent correction system for capacitor motor phase shift according to claim 6, characterized in that: The discharge switch circuit includes a rectifier bridge T5, a field effect transistor BT2, a PNP transistor BG7, an NPN transistor BG4, a diode D5, a resistor R11, a resistor R12, a resistor R13, a resistor R20, a resistor R25, a resistor R26, a voltage regulator diode W1 and a capacitor C4, one AC end of the rectifier bridge T5 is connected to one end of the phase-shift capacitor, the other AC end is connected to one end of the secondary winding connected to the power supply, the emitter of the NPN transistor BG4 is grounded, the base of the NPN transistor BG4 is simultaneously connected to the cathode of the diode D5 and one end of the resistor R12, the other end of the resistor R12 is connected to the emitter of the photocoupler OC2, the collector of the NPN transistor BG4 is simultaneously connected to one end of the resistor R13, one end of the resistor R26 and the gate of the field effect transistor BT2, the The other end of the resistor R26 is grounded, the other end of the resistor R13 is connected to the collector of the PNP transistor BG7, the emitter of the PNP transistor BG7 is simultaneously connected to the cathode of the Zener diode W1, one end of the resistor R20 and the positive electrode of the capacitor C4, the other end of the resistor R20 is connected between the resistor R21 and the resistor R22, the anode end of the Zener diode W1 is grounded, the negative electrode of the capacitor C4 is grounded, the base of the PNP transistor BG7 is connected to the collector of the NPN transistor BG5 through the resistor R25, the anode of the diode D5 is simultaneously connected to one end of the resistor R11 and the source of the field effect transistor BT2, the other end of the resistor R11 is grounded, the drain of the field effect transistor BT2 is connected to the cathode end of the rectifier bridge T5, and the anode end of the rectifier bridge T5 is grounded.

Images