Control of power electronic DC-DC converter

Abstract

The invention relates to a method (S1-S4, S4-1-S4-8, S6-S8) for controlling a power electronic DC converter (1) operated by means of a regulating device (2), having a primary side comprising at least two electronic switches (Q1-Q4) and a secondary side, which is galvanically separated therefrom and comprises at least one electronic switch (Q5-Q6), in the method, a guide variable ([Delta] t) and / or an adjustment variable of the adjustment device (2) are / is adapted by means of a BWHH algorithm. The invention also relates to a regulating device (2) for regulating a power electronic DC converter (1) having a primary side comprising at least two electronic switches (Q1-Q4) and a secondary side, which is galvanically separated therefrom and comprises at least one electronic switch (Q5, Q6), the regulating device (2) being designed to carry out the method (S1-S4, S4-1-S4-8, S6-S8).

Description

Technical Field

[0001] The invention relates to a method for controlling a power electronic DC converter operated by means of a control device, the DC converter having a primary side with at least two electronic switches and a secondary side galvanically separated therefrom and comprising at least one electronic switch, wherein in the method, an adaptation of a control variable and / or an adaptation of a control parameter of the control device is performed. The invention also relates to a control device for controlling a power electronic DC converter, the DC converter having a primary side with at least two electronic switches and a secondary side galvanically separated therefrom and comprising at least one electronic switch, wherein the control device is designed to implement the method. The invention further relates to a vehicle having at least one power electronic DC converter, the DC converter having a primary side with at least two electronic switches and a secondary side galvanically separated therefrom and comprising at least one electronic switch, wherein the DC converter can be controlled by means of the method. The invention can be applied in particular advantageously to electric vehicles, such as hybrid vehicles and in particular fully electric vehicles. Background Art

[0002] For automated driving functions in vehicles, especially electric vehicles, a reliable energy supply for safety-related components, such as steering and brakes, is required in the electrical onboard energy network. This results in safety requirements for energy supply that correspond to the Automotive Safety Integrity Levels (ASIL) to be classified. In order to prove functional safety in an early development phase, an onboard energy network simulation is implemented at the system level in order to ensure a reliable energy supply for safety-related components even in the event of a fault. In order to complete the numerical simulation of the entire onboard energy network simulation model within an acceptable simulation time, the simulation model should be solvable as computationally efficiently as possible. In particular, the DC converter including the semiconductor switches of the power electronics places very high demands on the simulation due to its high-frequency control.

[0003] For the computationally efficient modeling of the connected DC converter, so-called average value models or mean value models are known and available in the literature, such as: M. Winter, J. Taube, S. Moser, S. Schoenewolf, H.-G. Herzog: "Average Model of a Synchronous Half-Bridge DC / DC Converter Considering Losses and Dynamics," The 11th International Modelica Conference, 2015; M. Modabbernia: "An Improved State Space Average Model of Buck DC-DC Converter with all of the System Uncertainties", International Journal on Electrical Engineering and Informatics, March 2013, Volume 5, Pages 81 to 94 and L. Cao: "Small Signal Modeling for Phase-shifted PWM Converters with A Current Doubier Rectifier," IEEE Power Electronics Specialists Conference, 2007, Pages 423 to 429. These average value models do not simulate the entire switching characteristic, but rather simulate the average value.

[0004] Martin Baumann, Bert Haj Ali, Christoph Weissinger, Hans-Georg Herzog: "Efficient Small-Signal Algorithm for High Dynamic Phase-Shifted Full-Bridge Converters", Vehicle Power and Propulsion Conference, Gijón, Spanien, November 2020 An algorithm is disclosed that can efficiently replicate the dynamics of a phase-shifted full-bridge converter by iteratively calculating the diode conduction time and the corresponding state-space system. The proposed converter model includes an additional voltage source that describes the dynamics of the converter for different load-related downtime characteristics. The additional voltage is calculated based on a prediction of the leakage current during the switching cycle. The calculation time of the algorithm is reduced by 91% compared to the Switched model. The disclosure of Baumann et al. is fully incorporated into the present disclosure. Summary of the invention

[0005] The object of the present invention is to at least partially overcome the disadvantages of the prior art and in particular to provide a more reliable option for the energy supply of, in particular, safety-relevant components in a vehicle.

[0006] This object is achieved according to the features of the independent claims. Preferred embodiments can be derived in particular from the dependent claims.

[0007] The object is achieved by a method for controlling a power electronic DC converter operated by means of a regulating device, the DC converter having a primary side comprising at least two electronic switches and a secondary side galvanically separated therefrom and comprising at least one electronic switch, wherein in the method an adaptation of a control variable of the regulating device and / or an adaptation of a regulating parameter of the regulating device is carried out by means of a BWHH algorithm.

[0008] This method has the advantage that the inaccuracy of the available mean value model can be greatly reduced by using the BWHH algorithm. A high saving in computing time is maintained. This in turn enables a more efficient operation of the power electronic DC converter by adapting the control parameters and / or control parameters of the control device.

[0009] A power electronic DC converter is understood in particular to be a DC converter which can also convert relatively high electrical powers and which can be used for this purpose as an electronic switch, in particular a power semiconductor, such as a power MOSFET and an IGBT.

[0010] A further development is that the at least two electronic switches on the primary side are components of a bridge circuit, which is, for example, a half bridge including two electronic switches or a full bridge including four electronic switches. However, the number of electronic switches on the primary side is not limited and can also include, for example, three or more than four electronic switches, respectively, depending on the topology. This is particularly advantageous here.

[0011] The galvanic separation can be achieved, for example, by means of a transformer which is equipped with at least one primary coil and at least one secondary coil.

[0012] The at least one electronic switch on the secondary side is provided in particular for rectifying a voltage induced on the secondary-side transformer half.

[0013] A particularly advantageous embodiment is that the DC converter has a primary side with a full bridge and a secondary side with two electronic switches, the full bridge comprising four electronic switches, wherein the primary side and the secondary side are galvanically separated from one another by a transformer. In one embodiment, the DC converter is a phase shifter full bridge, since this operates particularly efficiently and can be flexibly adjusted.

[0014] The electronic switch may be, for example, a power semiconductor, such as a power transistor, such as a power MOSFET and an IGBT, but may also be, for example, a power diode or the like.

[0015] Depending on the topology, the DC converter can be designed as a step-up converter, a step-down converter or a combination thereof.

[0016] The "BWHH algorithm" is an algorithm which uses in a generalized manner the method described in Martin Baumann et al.: "Efficient Small-Signal Algorithm for High Dynamic Phase-Shifted Full-Bridge Converters", in particular in Chapter 3 for a phase shifted full bridge (PSFB), in order to use the leakage inductance L through the primary side to k The current i Lk The prediction of the on-duration loss d L and / or additional voltage u add However, Baumann et al. describe in detail the Figure 1 The BWHH algorithm described in the following phase shifter full bridge can also be applied to other topologies of DC converters when the switching scheme is known. In this way, the BWHH algorithm can also be adapted to DC converters including half-bridges on the primary side, simple step-up or step-down converters, etc.

[0017] In particular, the switch-on time loss is calculated during step-down conversion, and in particular, the additional voltage is calculated during step-up conversion. If necessary, the switch-on time loss during step-up conversion can be calculated or at least evaluated from the additional voltage.

[0018] A further development is that the pilot variable is a switch-on duration loss d L and / or additional voltage u add The guiding variable can also be called a regulating reference.

[0019] The adaptation of the control parameters of the control device by means of the BWHH algorithm comprises in particular the adaptation of the control parameters by means of an output parameter of the BWHH algorithm, namely the switch-on time loss d L and / or additional voltage u add The control parameter may be, for example, a common parameter of the controller of the control device, for example, for a PI controller, the parameter is K p and K i , the parameter for the PID regulator is K p , K i and K d In principle, there are no restrictions on the type of controller for which the control parameters can be adapted using the BWHH algorithm. In particular, the control parameters can be adapted with the goal of achieving advantageous control dynamics (eg short transition state durations and / or small overshoot amplitudes).

[0020] One embodiment provides that the DC converter is regulated by means of a cascaded current-voltage regulator. The adaptable regulating variable can in particular be a regulating variable of a current regulator and / or a voltage regulator of the current-voltage regulator.

[0021] In one embodiment, the BWHH algorithm calculates the switch-on duration loss and / or the additional voltage from the following input variables: the input voltage applied to the primary side of the DC converter, the duty cycle output (for example by a current regulator of a current-voltage regulator), the output voltage output by the secondary side of the DC converter and the output current of the secondary side of the DC converter.

[0022] In one embodiment, the BWHH algorithm is composed of the above-mentioned input parameters

[0023] -First calculate the ripple current,

[0024] - From the ripple current, calculate the current i through the transformer half on the primary side or the corresponding leakage inductance Lk The initial value of

[0025] - successively calculating for each phase of the switching scheme of the DC converter the current i at the end of this phase Lk and

[0026] At the end of the last phase of the switching strategy, the switch-on time losses and / or the additional voltage are calculated therefrom.

[0027] This achieves the advantage that the switch-on time losses and / or the additional voltage can be calculated from simple input variables, despite the highly dynamic system states in the DC converter, which describe the collection of the individual states of all energy storage devices (e.g., inductors, capacitors, etc.) in the system under consideration for a certain common (common) position of the switches. A switching state of the electronic (primary and secondary) switches is assigned to each phase, wherein these switching states and their sequence are derived from the switching diagram. Usually, a plurality of system states (typically written as vectors or in vector form) are assigned to each switching state. Thus, the current i at the beginning of a phase is Lk The value of the current i at the end of the phase Lk The value of is different. Therefore, if the current i at the end of each phase of the switching scheme is calculated successively, Lk , then this means that first from the current i Lk Starting from the initial value of , it is calculated how the current behaves in the first phase or what its value is at the end of the first phase. This value at the end of the first phase is used as an input variable for the subsequent second phase and then calculated, what its value is at the end of the second phase, and so on.

[0028] In one embodiment, the command variable corresponds to a (reference) time delay which is calculated as a switch-on time loss d L The time delay describes the extent of the delayed switching of the electronic switch on the secondary side. A further development is to compare the calculated (reference) time delay with the measured time delay and use the difference as a control deviation. The control deviation can then be supplied, for example, to an integrated regulator, which calculates a duration therefrom, which is used, for example, in a modulator to generate a switching pattern for the switch on the secondary side.

[0029] The object is also achieved by a control device (also referred to as control device or control loop) for controlling a power electronic DC converter, the DC converter having a primary side including at least two electronic switches and a secondary side galvanically separated therefrom and including at least one electronic switch, in particular as described above, wherein the control device is designed to implement the method described above. The control device can be designed similarly to it and vice versa and has the same advantages.

[0030] In this way, the regulating device can be a cascaded current-voltage-regulating device. The BWHH algorithm can be implemented in hardware or software technology. The regulating device can, for example, include a PI or PID current regulator and a PI or PID voltage regulator.

[0031] The object is also achieved by a vehicle having at least one power electronic DC converter having a primary side comprising at least two electronic switches and a secondary side galvanically separated therefrom and comprising at least one electronic switch, wherein the DC converter is controllable by means of the method described above. The vehicle can be designed similarly to the method and / or the control device, and vice versa, and has the same advantages.

[0032] In one embodiment, the DC converter is provided for converting the voltage between two partial energy onboard power systems of the vehicle with different voltage levels. The two partial energy onboard power systems can be, for example, a high voltage (HV) partial energy onboard power system with a first supply voltage and a low voltage (NV) partial energy onboard power system with a second supply voltage, wherein the first supply voltage is greater than the second supply voltage. The first supply voltage can be, for example, between 48 V and 800 V or even higher. The second supply voltage can be, for example, between 12 V and 60 V.

[0033] The vehicle may be, for example, a vehicle comprising an internal combustion engine or (particularly advantageously) an electric vehicle, such as a hybrid vehicle or a fully electrically driven vehicle. The vehicle may be, for example, a land vehicle such as a car, a motorcycle, a bus, a truck, etc., an air vehicle such as an airplane, a helicopter, etc., or a water vehicle such as a ship, etc. BRIEF DESCRIPTION OF THE DRAWINGS

[0034] The above-mentioned properties, features and advantages of the present invention and the manner and method of achieving them become more apparent and more clearly understandable in conjunction with the following schematic description of an embodiment, which is explained in more detail in conjunction with the drawings.

[0035] Figure 1 A known DC converter in the form of a phase shifter full bridge ("PSFB") is shown;

[0036] Figure 2 Shown for adjustment Figure 1 Sketch of the adjustment structure of the phase shifter full bridge in;

[0037] Figure 3 A possible procedure for calculating the switch-on time loss and the additional voltage using the BWHH algorithm is shown; and

[0038] Figure 4 Show Figure 3 A sub-process of a process in . DETAILED DESCRIPTION

[0039] Figure 1 The equivalent circuit diagram of a DC converter in the form of a phase shifter full bridge 1 is shown, as in Baumann et al.: "Efficient Small-Signal Algorithm for High Dynamic Phase-Shifted Full-Bridge Converters" Figure 1 The phase shifter full bridge 1 can be used in particular to convert voltage between two partial energy onboard power systems of a vehicle F, in particular a fully electric vehicle F, with different voltage levels, in particular to step down the voltage of the HV partial onboard power system into the voltage of the NV partial onboard power system or vice versa.

[0040] The full-bridge inverter on the primary side in the form of a four-quadrant regulator contains an electronic switch Q i , where i=1, ..., 4, the electronic switch contains not only a free-wheeling diode (body diode) with reverse polarity but also a drain-source capacitor. The full bridge is connected to a low-inductance planar transformer with a center tap, which dominates the leakage inductance L of the transformer half on the primary side. k The impedance of the primary side transformer half R p The secondary rectifier circuit includes two electronic switches Q5, Q6 and an inductor capacitor filter. The inductor L on the secondary side f Exceeds the primary side leakage inductance L k An order of magnitude. Impedance R s The output capacitor C includes the impedance of the transformer, shunt and PCB vias. o With its parasitic impedance R C Modeling.

[0041] Figure 2The schematic diagram shows a cascaded current-voltage control arrangement 2 for controlling a phase shifter full bridge 1 or a method for controlling a phase shifter full bridge 1 operated with the cascaded current-voltage control arrangement. The control arrangement 2 is simply referred to below as “control device” 2 without limiting the generality.

[0042] The regulating device 2 has a voltage regulator C u , for example a PI or PID regulator, which receives the control deviation e as an input variable u . Adjustment deviation e u Corresponding to the theoretical output voltage u of the phase shifter full bridge 1 ref The difference between the actual output voltage u, where u corresponds to Figure 1 The output voltage V o , that is, u=V o .

[0043] Voltage Regulator C u Given the filter inductance L through the secondary side f The theoretical value of the current i L,ref As the adjustment parameter. f The theoretical value of the current i L,ref and the actual value i L The difference between the calculated adjustment deviation e i As input variable, it is fed into the current regulator C i , for example in a PI or PID regulator, the current regulator transmits the duty cycle (duty factor, English "duty cycle") d as an output signal to the control link E(s). The control link E(s) simulates a delay of the duty cycle d, which is generated, for example, by the calculation time of the microcontroller, "s" being the associated Laplace variable.

[0044] The phase shifter full bridge 1 can be described in terms of control technology as a control path, which includes the calculation of the actual current variable i from the duty cycle d. L The first conversion block G iL,d and the actual current parameter i L The first conversion block G calculates the actual output voltage u iL,d .

[0045] The algorithm described in Chapter 3 of Baumann et al. can now be used to calculate the switch-on time loss d L and additional voltage u add , in order to improve the control dynamics, for example by means of a faster start-up behavior and / or to enable a more efficient operation of the phase shifter full bridge 1 . For this purpose, the duty cycle d, the output voltage u=V o, output current I o and input voltage V in is input to the calculation block 3, where the algorithm is implemented. Output current I o You can use the conversion block G Io,iL The filter inductor L f The actual value of the current i L can be calculated or can be measured directly at the output of the phase shifter full bridge 1 .

[0046] The calculation block 3 can thereby calculate the on-time loss (duty cycle loss, English “duty cycle loss”) d during the step-down conversion, for example as described in Baumann et al. L , calculate the additional voltage u during step-up conversion and no-load operation add . Switch-on duration loss d L Now, as indicated by calculation block 4, it is used to calculate the (reference / theoretical) time delay Δt ref =f(d L ), which describes the extent of the delayed switching of the switches Q5 and / or Q6, which is delayed by the calculated switch-on time loss d L Conclude.

[0047] The attempt is to place the actually existing, for example measured, time delay Δt on the reference time delay Δt ref To this end, the measured time delay Δt is determined by comparing it to the reference time delay Δt ref The difference Δt And it is sent to the regulator C as the control deviation Δt . Regulator C Δt From this, a switching time delay dT for the switches Q5 and / or Q6 is calculated as a control variable, which is used in the modulator (as shown in the figure above) to generate the switching pattern of the switches Q5 and Q6. Δt In particular, these are integrated controllers, for example PI or PID controllers.

[0048] Furthermore, the switch-on time loss d L (represented here by matching block 5) can be used to adjust the regulator C u and C i The control parameters, such as adjusting K for the PID controller p , K i and K dThe control parameters are adapted to the existing control paths of the onboard power system, so that the phase shifter full bridge 1 has better dynamics. This achieves the advantage that the controller can operate faster (e.g. with lower “settling time”, lower “overshoot”, etc.) and / or more robustly (e.g. more stable at critical operating points).

[0049] Although the control device 2 has been described more precisely for the case of a step-down converter, it can also be used for a step-up converter. In the step-up converter, the switch-on time loss d L Calculate the additional voltage u add . Additional voltage u add For example, it is also possible to convert the equivalent switch-on duration loss d into the equivalent switch-on duration loss d by calculation block 3. L And the regulation path is then used similarly to the step-down conversion.

[0050] Figure 3 A possible flow of a BWHH algorithm for a DC converter is shown, wherein the operation of the BWHH algorithm can be divided into four stages p1, p2, p3 and p4, namely the first ("power output") stage p1, the second ("no-load operation") stage p2, the third ("on-duration loss") stage p3 and the fourth ("no-load operation") stage p4. The BWHH algorithm can correspond in particular to the algorithm described in Chapter 3 of Baumann et al., but is not limited thereto. The four-stage BWHH algorithm can be used, for example, for a phase shifter full bridge 1. For DC converters having other topologies and / or other switching schemes, fewer or more than four stages can also be set.

[0051] In step S1, the BWHH algorithm is initialized by setting the input voltage V in , output voltage V o , output current I o and duty cycle d input.

[0052] The ripple current I is calculated in step S2. r .

[0053] In step S3, the ripple current I r Calculate the leakage inductance L through the primary side k The current i Lk The initial value of the current i Lk Corresponds to the current through the transformer half on the primary side.

[0054] In step S4, for the power output phase p1, the current i LKThe value of the current i present at the end of the power output phase p1 is determined based on the state space equations describing the DC converter and the possible system state x LK The value of and the possible system states x present in the set of possible system states x at the end of the power output phase p1. The system state x here describes the set of individual states of all energy storage devices (e.g. inductors, capacitors, etc.) of the system under consideration, here of the DC converter, for a certain common (switching) position of the switches Q1 to Q6. Exactly one switching position is assigned to a phase, and a phase may include a plurality of system states x. The listing of state space equations is known in principle and is therefore not explained in further detail.

[0055] Using the current i at the end of the power output phase p1 Lk and the system state x calculated at the end of the power output phase p1, the process proceeds to step S5, in which the (time-varying) current i at the end of the no-load operation phase p2 is calculated. Lk .

[0056] Next, the process proceeds to step S6, in which, similar to step S4, the current i at the end of the no-load operation phase p2 is used for the power output phase p1. Lk Based on the state space equations and the possible system state x, the current i at the end of the on-time loss phase p3 is determined: Lk In addition, the system state x that is actually present at the end of the switch-on duration loss phase p3 is determined from the set of possible system states x.

[0057] Using the current i at the end of the on-time loss phase p3 Lk and the system state x calculated at the end of the switch-on time loss phase p3, the process proceeds to step S7, in which the current i at the end of the no-load operation phase p4 is calculated analogously to step S5. Lk .

[0058] In step S8, the current i present at the end of the no-load operation phase p4 is then Lk Calculation of the switch-on duration loss d L (in step-down conversion) and / or additional voltage u add (during step-up conversion and in no-load operation).

[0059] This procedure is described in detail in Baumann et al. Figure 1 The following description of the phase shifter full bridge / PSFB DC converter can, however, also be applied to other DC converter topologies when the corresponding switching schemes are known. These other combinations of topologies and switching schemes can include more or fewer than four phases.

[0060] Figure 4 A more detailed description of an example of step S4 is shown.

[0061] In the first initialization phase S4-1, the current i Lk The initial value calculated in step S3 determines the initial system state x(i) from the set of possible system states x with different i in this phase p1 as the current system state. t=0 also applies here.

[0062] In step S4-2, it is checked whether the time t that has elapsed so far is less than the predetermined fault time T d , for example, 100ns, that is, whether t <T d , alternatively whether t≤T d This is the case at t=0 according to step S4-1, and the process then proceeds to step S4-3.

[0063] In step S4 - 3 , it is checked whether there is a system state x(i), for example i=0, in which none of the (body) diodes of the switches Q1 to Q6 is conducting.

[0064] If this is the case ("J"), in step S4-4 the change in the system state x is calculated for a predetermined time segment or time window and then branched to step S4-2. In step S4-2 a check is made to see whether the time t of the now increased time segment is less than or equal to the downtime T d If this is the case ("J"), the process goes back to step S4-3.

[0065] However, if it is detected in step S4-3 that the system state x(i) is no longer at i=0 because at least one of the body diodes of switches Q1 to Q6 is conducting ("N"), the process proceeds to step S4-5, in which a check is performed to determine whether a specific body diode, here for example the body diode of switch Q2, is conducting.

[0066] If this is the case ("J"), then in step S4-6 the change in the system state x is calculated for a predetermined time segment or time window similarly to step 4-4 and then branched to step S4-2. In step S4-2 a check is again made to see whether the time t of the now increased time segment is less than or equal to the downtime T d If this is still the case ("J"), the process goes back to step S4-3.

[0067] However, if the check in step S4-5 shows that the body diode of the switch Q2 determined there does not conduct current ("N"), then the process proceeds to step S4-7. If this step S4-7 corresponds to the last available system state x, this system state must exist, so that the process then proceeds to step S4-8, in which the change in system state x is calculated for a predetermined time segment or time window similarly to step 4-4 and then branches to step S4-2. In step S4-2, a check is performed to see whether the time t of the now increased time segment is less than or less than or equal to the idle time T d If this is still the case ("J"), the process returns to step S4-3, etc.

[0068] However, if the downtime T is reached in step S4-2 d ("N"), the output current i Lk The currently valid value of and the currently valid system state x are taken and used as input or input variable for step S5.

[0069] Currently, only three diode conduction states can exist in the first phase p1, i.e., no body diode conduction current in each body diode (i=0), only body diode conduction current of switch Q2 (i=2) or only body diode conduction current of switch Q4 (i=4). In DC converters with other topologies and / or other switching schemes, other system states may be possible.

[0070] It goes without saying that the invention is not restricted to the exemplary embodiments shown.

[0071] Generally, “one”, “an” etc. can be understood as singular or plural, especially in the sense of “at least one” or “one or more” etc., as long as this is not explicitly excluded, for example by the expression “exactly one” etc.

[0072] Numerical specifications may also include the exact values ​​given and the usual error ranges, unless expressly excluded.

[0073] Reference numerals list

[0074] 1 Phase Shifter Full Bridge

[0075] 2. Adjustment device

[0076] 3 Calculation Block

[0077] 4 Calculation Blocks

[0078] 5 matching blocks

[0079] C i Current Regulator

[0080] Cu Voltage Regulator

[0081] C Δt Regulator

[0082] dDuty cycle

[0083] d L On-time loss

[0084] E(s) adjustment stage

[0085] e i Adjustment deviation

[0086] e u Adjustment deviation

[0087] F Vehicle

[0088] G iL,d Conversion Block

[0089] G Io,iL Conversion Block

[0090] G u,iL Conversion Block

[0091] i L The actual value of the current through the filter inductor on the secondary side

[0092] i Lk The actual value of the current through the leakage inductance of the transformer half on the primary side

[0093] i L,ref Theoretical value of the current through the filter inductor on the secondary side

[0094] I o Output Current

[0095] L f Filter inductor on the secondary side

[0096] L k Leakage inductance of the transformer half on the primary side

[0097] Q i The i-th electronic switch

[0098] R s impedance

[0099] R p The impedance of the transformer half on the primary side

[0100] S1-S7 Method Steps

[0101] S4-1-S4-5 sub-steps

[0102] t time

[0103] Δt time delay

[0104] Δt ref Theoretical time delay

[0105] Actual output voltage

[0106] u add Additional voltage

[0107] u ref Theoretical output voltage

[0108] V in Input voltage

[0109] V o Output voltage

[0110] x vector in state space

Claims

1. A method (S1-S4, S4-1-S4-8, S6-S8) for controlling a power electronic DC converter (1) operated by means of a regulating device (2), the DC converter having a primary side including at least two electronic switches (Q1-Q4) and a secondary side galvanically isolated therefrom and including at least one electronic switch (Q5-Q6), wherein: In the method described, the BWHH algorithm is used to perform - Adaptation of the control variable (Δt) and / or - Adaptation of the control parameters of the control device (2).

2. The method (S1-S4, S4-1-S4-8, S6-S8) according to claim 1, wherein: The DC converter (1) is regulated by means of a cascaded current and voltage regulator (2), wherein the adaptable regulation parameters can include a current regulator (C i ) and / or the voltage regulator (C u ) adjustment parameters.

3. The method (S1-S4, S4-1-S4-8, S6-S8) according to any of the above claims, wherein: The BWHH algorithm is calculated from the input parameters - an input voltage (V in ), - duty cycle (d), - the output voltage (V o )and - an output current (I o ), connection duration loss (d L ) and / or additional voltage (u add ).

4. The method (S1-S4, S4-1-S4-8, S6-S8) according to claim 3, wherein: The BWHH algorithm is composed of the input parameters (V in 、V o ,I o d) -First calculate the (S2) ripple current, - calculated from the ripple current (S3) through the transformer half on the primary side or the corresponding leakage inductance (L k ) of the current (i Lk ), - successively calculating (S4-S7) the current (i Lk )and At the end of the last phase (p4) of the switching scheme, the switch-on duration loss (d L ) and / or additional voltage (u add ).

5. The method according to any one of the above claims (S1-S4, S4-1-S4-8, S6-S8), wherein: The pilot variable corresponds to the reference time delay (Δt ref ), the reference time delay is used as the switch-on duration loss (d L ) is calculated as a function of, where the reference time delay (Δt ref ) describes the extent of the delayed switching of the at least one electronic switch (Q5, Q6) on the secondary side.

6. The method according to any one of the preceding claims (S1-S4, S4-1-S4-8, S6-S8), wherein: The DC converter (1) has a primary side including a full bridge and a secondary side including two electronic switches (Q5, Q6), wherein the full bridge includes four electronic switches (Q1-Q4), wherein the primary side and the secondary side are galvanically separated from each other by a transformer.

7. The method (S1-S4, S4-1-S4-8, S6-S8) according to claim 6, wherein: The DC converter (1) is a phase shifter full bridge.

8. A regulating device (2) for regulating a power electronic DC converter (1), the DC converter having a primary side with at least two electronic switches (Q1-Q4) and a secondary side galvanically isolated therefrom and comprising at least one electronic switch (Q5, Q6), wherein: The regulating device (2) is designed to carry out a method (S1-S4, S4-1-S4-8, S6-S8) according to one of the preceding claims.

9. A vehicle (F) comprising at least one power electronic DC converter (1), the DC converter having a primary side comprising at least two electronic switches (Q1-Q4) and a secondary side galvanically isolated therefrom and comprising at least one electronic switch (Q5, Q6), wherein: The DC converter (1) is controllable, in particular regulatable, by means of a method (S1-S4, S4-1-S4-8, S6-S8) according to one of claims 1 to 7.

10. The vehicle (F) according to claim 9, wherein: The DC converter (1) is provided for converting the voltage between two onboard energy supply systems of the vehicle (F) having different voltage levels.

11. The vehicle (F) according to any one of claims 9 to 10, wherein: The vehicle (F) is an electric vehicle.

Images