A resonant high voltage converter and a single cycle energy control method

Abstract

The present application relates to a resonant high-voltage converter and a single-cycle energy control method, comprising an LCC resonant cavity circuit, a full-bridge inverter circuit, an energy control inner loop circuit, an output voltage control outer loop circuit, a processing circuit and a first monostable trigger. A first voltage and a first current are multiplied by a multiplier and then input into an integrator for integration to obtain control input energy; a second voltage is subtracted from a reference voltage setting value and then subjected to PID operation to obtain reference energy; when the control input energy is greater than or equal to the reference energy, a processing signal is generated; when the first monostable trigger obtains the processing signal, the first monostable trigger controls the LCC resonant cavity circuit to flip from the first state to the second state.

Description

Technical Field

[0001] The present application relates to the technical field of resonant high-voltage converters, and particularly to a resonant high-voltage converter and a single-cycle energy control method. Background Art

[0002] Traditional high-voltage DC conversion consists of a power-frequency transformer with a high step-up ratio and a high-voltage silicon stack, which has problems such as large volume, low efficiency, being greatly affected by power grid fluctuations, and lacking the ability to adjust the output voltage. With the increasing requirements for power supply quality by high-voltage equipment, switched-mode converters have received extensive attention in high-voltage application scenarios due to advantages such as a wide voltage regulation range, good soft-switching characteristics, small voltage ripple, and high power density. Among them, the phase-shifted full-bridge converter is widely used because of its wide voltage regulation range and high power density, but there is a problem that it is difficult to achieve soft switching of the lagging bridge arm under light load. In contrast, resonant converters are widely used in high-power scenarios due to their excellent soft-switching characteristics. Among them, the LLC resonant converter can simultaneously achieve zero-voltage turn-on of the primary switching tube and zero-current turn-off of the secondary diode, and has high light-load efficiency. However, in high-voltage application scenarios, the parameters of the resonant cavity are easily affected by the output parasitic capacitance of the high-ratio transformer. The LCC resonant converter is widely used in high-voltage output scenarios because it can utilize the output parasitic capacitance of the converter as part of the resonant capacitance.

[0003] The existing single-cycle energy control method for resonant high-voltage DC converters is difficult to meet the requirements of fast voltage regulation under load mutation and stable voltage output under high-frequency input disturbances. Summary of the Invention

[0004] To solve or partially solve the problems existing in the related art, the present application provides a resonant high-voltage converter and a single-cycle energy control method, which can solve the technical problem that the existing single-cycle energy control method for resonant high-voltage DC converters is difficult to meet the requirements of fast voltage regulation under load mutation and stable voltage output under high-frequency input disturbances.

[0005] The first aspect of the present application provides a resonant high-voltage converter, including:

[0006] An LCC resonant cavity circuit, having a first state and a second state;

[0007] A full-bridge inverter circuit, the input end of the full-bridge inverter circuit is electrically connected to the LCC resonant cavity circuit. When the LCC resonant cavity circuit is in the first state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the forward direction. When the LCC resonant cavity circuit is in the second state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the reverse direction;

[0008] An inner energy control loop circuit, having an integrator and a multiplier, is configured to sample the input voltage of the full-bridge inverter circuit to obtain a first voltage and sample the input current of the full-bridge inverter circuit to obtain a first current. After multiplying the first voltage and the first current by the multiplier, the result is input into the integrator for integration to obtain the controlled input energy;

[0009] An outer output voltage control loop circuit is configured to sample the voltage output at the output terminal of the full-bridge inverter circuit to obtain a second voltage. After calculating the difference between the second voltage and a reference voltage set value and performing a PID operation, a reference energy is obtained;

[0010] A processing circuit, electrically connected to the inner energy control loop circuit and the outer output voltage control loop circuit, is configured to obtain the controlled input energy and the reference energy, and generate a processing signal when the controlled input energy is greater than or equal to the reference energy; and

[0011] A first monostable flip-flop, electrically connected to the processing circuit and the LCC resonant cavity circuit, is configured to control the LCC resonant cavity circuit to flip from the first state to the second state when the processing signal is obtained.

[0012] In some embodiments, it further includes:

[0013] A DC input circuit, electrically connected to the LCC resonant cavity circuit, is configured to supply power to the LCC resonant cavity circuit.

[0014] In some embodiments, it further includes:

[0015] A second monostable flip-flop, electrically connected to the processing circuit and the integrator, is configured to send a clearing signal to the integrator when the processing signal is obtained. After obtaining the clearing signal, the integrator clears the integration therein.

[0016] In some embodiments, it further includes:

[0017] A light-load drive compensation circuit, electrically connected to the processing circuit, the inner energy control loop circuit, and the first monostable flip-flop, is configured to generate a compensation signal and send it to the first monostable flip-flop when the processing signal and the controlled input energy are obtained.

[0018] In some embodiments, the light-load drive compensation circuit includes:

[0019] A third monostable flip-flop, electrically connected to the processing circuit, is configured to generate a trigger signal when the processing signal is obtained;

[0020] A differentiator, electrically connected to the inner energy control loop circuit, is configured to obtain the control input energy and determine that the zero-crossing point after the control input energy passes through the differentiator is the peak energy point;

[0021] A first comparator, the first input terminal of the comparator is electrically connected to the differentiator, the second input terminal of the comparator is grounded, and the comparator is configured to generate a square wave signal when the zero-crossing point after the control input energy passes through the differentiator is the peak energy point;

[0022] An AND gate sub-circuit, electrically connected to the third monostable flip-flop, the first comparator and the first monostable flip-flop, is configured to generate a compensation signal and send it to the first monostable flip-flop when the trigger signal and the square wave signal are obtained.

[0023] In some embodiments, it further includes:

[0024] An OR gate circuit, electrically connected to the processing circuit, the AND gate sub-circuit and the first monostable flip-flop, is configured to generate a first trigger signal and send the first trigger signal to the first monostable flip-flop when the compensation signal is obtained, or generate a second trigger signal and send the second trigger signal to the first monostable flip-flop when the processing signal is obtained.

[0025] In some embodiments, it further includes: a hybrid symmetric voltage doubler rectifier circuit, electrically connected to the input terminal of the full-bridge inverter circuit, and the second voltage is the output voltage of the hybrid symmetric voltage doubler rectifier circuit.

[0026] In some embodiments, the inner energy control loop circuit includes:

[0027] A first sampler, configured to sample the input voltage of the full-bridge inverter circuit to obtain a first voltage;

[0028] A second sampler, configured to sample the input current of the full-bridge inverter circuit to obtain a first current;

[0029] A multiplier, electrically connected to the first sampler and the second sampler, is configured to multiply the first voltage and the second voltage to obtain a product value; and

[0030] An integrator, electrically connected to the multiplier and the processing circuit, is configured to integrate according to the product value to obtain the control input energy and deliver the control input energy to the processing circuit.

[0031] In some embodiments, the outer output voltage control loop circuit includes:

[0032] A third sampler for sampling the voltage output from the output terminal of the full-bridge inverter circuit to obtain a second voltage;

[0033] An analog-to-digital converter electrically connected to the third sampler for performing analog-to-digital conversion on the second voltage to obtain a converted second voltage;

[0034] A differencer electrically connected to the analog-to-digital converter for taking the difference between the converted second voltage and a reference voltage set value to obtain a second voltage after taking the difference;

[0035] A PID feedback unit electrically connected to the analog-to-digital converter for performing PID operation on the second voltage after taking the difference to obtain a specified reference energy;

[0036] A digital-to-analog converter electrically connected to the PID feedback unit and the processing circuit for performing digital-to-analog conversion on the specified reference energy to obtain the reference energy and sending the reference energy to the processing circuit.

[0037] A single-cycle energy control method for a resonant high-voltage converter according to a second aspect of the present application includes the resonant high-voltage converter according to any one of the above embodiments. The single-cycle energy control method includes:

[0038] Sampling the input voltage of the full-bridge inverter circuit to obtain a first voltage and sampling the input current of the full-bridge inverter circuit to obtain a first current, multiplying the first voltage and the first current through a multiplier and then inputting the result into an integrator for integration to obtain a controlled input energy;

[0039] Sampling the voltage output from the output terminal of the full-bridge inverter circuit to obtain a second voltage, taking the difference between the second voltage and a reference voltage set value and then performing PID operation to obtain a reference energy;

[0040] Generating a processing signal when the controlled input energy is greater than or equal to the reference energy;

[0041] When a first monostable flip-flop obtains the processing signal, the first monostable flip-flop controls the LCC resonant cavity circuit to flip from the first state to the second state;

[0042] Wherein, when the LCC resonant cavity circuit is in the first state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the forward direction, and when the LCC resonant cavity circuit is in the second state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the reverse direction.

[0043] The technical solution provided by the present application may include the following beneficial effects:

[0044] The resonant high-voltage converter and single-cycle energy control method of the present application. The resonant high-voltage converter includes an LCC resonant cavity circuit, a full-bridge inverter circuit, an energy control inner loop circuit, an output voltage control outer loop circuit, a processing circuit, and a first monostable flip-flop. The input voltage of the full-bridge inverter circuit is sampled to obtain a first voltage, and the input current of the full-bridge inverter circuit is sampled to obtain a first current. After multiplying the first voltage and the first current through a multiplier, the result is input into an integrator for integration to obtain the controlled input energy. The voltage output at the output terminal of the full-bridge inverter circuit is sampled to obtain a second voltage. After calculating the difference between the second voltage and the reference voltage set value through PID operation, the reference energy is obtained. When the controlled input energy is greater than or equal to the reference energy, a processing signal is generated. When the first monostable flip-flop obtains the processing signal, the first monostable flip-flop controls the LCC resonant cavity circuit to flip from the first state to the second state. Wherein, when the LCC resonant cavity circuit is in the first state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in a positive manner, and when the LCC resonant cavity circuit is in the second state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in a reverse manner. Thus, it can effectively solve the technical problem that the existing single-cycle energy control method of the resonant high-voltage DC converter is difficult to meet the requirements of fast voltage regulation under load mutation and stable voltage output under high-frequency input disturbance.

[0045] Moreover, the input energy information in each period is introduced into the full-bridge inverter circuit of the resonant high-voltage converter in this embodiment, which improves the dynamic response performance of the resonant high-voltage converter to load mutation and input voltage fluctuation, and helps to reduce the requirement for the input DC capacitor and improve the overall power density of the machine.

[0046] In addition, the resonant high-voltage converter in this embodiment has a fast dynamic response speed during load mutation and output short circuit, and obtains the controlled input energy through a multiplier and an integrator, avoiding complex calculation processes. At the same time, the first voltage obtained by sampling the input voltage of the full-bridge inverter circuit is introduced into the energy control inner loop circuit, enhancing the output voltage stability during input fluctuation, which is beneficial to reducing the DC bus capacitor and improving the overall power density of the machine.

[0047] In some embodiments, a first sampler samples the input voltage of the full-bridge inverter circuit to obtain a first voltage; a second sampler samples the input current of the full-bridge inverter circuit to obtain a first current; a multiplier multiplies the first voltage and the second voltage to obtain a product value; and an integrator integrates according to the product value to obtain the controlled input energy and delivers the controlled input energy to the processing circuit.

[0048] In some embodiments, a second voltage is obtained by sampling the voltage output from the output terminal of the full-bridge inverter circuit through a third sampler; an analog-to-digital converter performs analog-to-digital conversion on the second voltage to obtain the converted second voltage; a subtractor subtracts the converted second voltage from a reference voltage set value to obtain the subtracted second voltage; a PID feedback controller performs a PID operation on the subtracted second voltage to obtain a specified reference energy; a digital-to-analog converter performs digital-to-analog conversion on the specified reference energy to obtain the reference energy and sends the reference energy to the processing circuit.

[0049] In some embodiments, when a processing signal is obtained, a second monostable flip-flop sends a clearing signal to the integrator, and the integrator clears the integration therein after obtaining the clearing signal.

[0050] In some embodiments, it further includes:

[0051] When the light-load drive compensation circuit obtains the processing signal and the control input energy, it generates a compensation signal and sends it to the first monostable flip-flop.

[0052] In this embodiment, when the light-load drive compensation circuit obtains the processing signal and the control input energy, it can generate a compensation signal and send it to the first monostable flip-flop U2, thereby driving the flip signal to control the rapid flipping of the closing of the slave switching tubes S1 and S4 (the first state) to the closing of the switching tubes S2 and S3, realizing maximum power transfer and rapid boost. Thus, it effectively solves the problem that during the process of the resonant high-voltage converter switching from light load to heavy load, the control input energy W int cannot reach the reference energy W within a single cycle ref resulting in the output signal of the specified comparator U7 continuously maintaining a low level and the drive signals of the switching tubes S1 - S4 in the flip circuit U1 not flipping.

[0053] In some embodiments, when the third monostable flip-flop obtains the processing signal, it generates a trigger signal;

[0054] When the differentiator obtains the control input energy and determines that the zero-crossing point of the control input energy after passing through the differentiator is the peak energy point;

[0055] When the zero-crossing point of the control input energy after passing through the differentiator is the peak energy point, the first comparator generates a square wave signal;

[0056] When the AND gate sub-circuit obtains the trigger signal and the square wave signal, it generates a compensation signal and sends it to the first monostable flip-flop.

[0057] In this embodiment, the differentiator obtains the control input energy, and generates a peak signal when the zero crossing point after the control input energy passes through the differentiator is the peak energy point. By sending the peak signal to the first input terminal of the first comparator U6, and grounding the second input terminal of the first comparator U6, a square wave signal is generated when the zero crossing point after the control input energy passes through the differentiator is the peak energy point; and the square wave signal is input into the second input terminal of the gate circuit U4. When the trigger signal and the square wave signal are obtained, a compensation signal is generated and sent to the first monostable flip-flop. Thereby driving the flip signal control to quickly flip from the closure of the switching transistors S1 and S4 (the first state) to the closure of the switching transistors S2 and S3, realizing maximum power transfer for rapid boost.

[0058] Among them, when the inner energy control loop circuit is working properly, the designated comparator U7 generates a low-level narrow pulse signal through the third monostable flip-flop U5, and is disabled through the AND gate circuit U4, and does not drive the light load drive compensation circuit, avoiding the conflict between the inner energy control loop circuit and the light load drive compensation circuit. Thus, it effectively solves the problem that during the process of the resonant high-voltage converter switching from light load to heavy load in the operating state, the control input energy W int cannot reach the reference energy W within a single cycle ref resulting in the output signal of the designated comparator U7 continuously maintaining a low level and the drive signals of the switching transistors S1 - S4 in the flip circuit U1 not flipping.

[0059] In some embodiments, when the OR gate circuit obtains the compensation signal, it generates a first trigger signal and sends the first trigger signal to the first monostable flip-flop, or when it obtains the processing signal, it generates a second trigger signal and sends the second trigger signal to the first monostable flip-flop.

[0060] In this embodiment, as long as the OR gate circuit U3 obtains the compensation signal or the processing signal, it can generate the corresponding first trigger signal or second trigger signal. That is to say, through the OR gate circuit U3, the situation of ordinary load mutation or input voltage fluctuation of the resonant high-voltage converter and the situation of the resonant high-voltage converter switching from light load to heavy load in the operating state can be distinguished, avoiding conflict situations.

[0061] It should be understood that the above general description and the following detailed description are only exemplary and explanatory, and cannot limit this application. Brief Description of the Drawings

[0062] The above and other objects, features, and advantages of the present application will become more apparent by describing exemplary embodiments of the present application in more detail with reference to the accompanying drawings. In the exemplary embodiments of the present application, the same reference numerals generally represent the same components.

[0063] Figure 1 FIG. is a schematic circuit diagram of the main circuit and the control circuit of the resonant high-voltage converter shown in the embodiments of the present application, where (a) is a schematic circuit diagram of the main circuit of the resonant high-voltage converter shown in the embodiments of the present application; (b) is a schematic circuit diagram of the control circuit of the resonant high-voltage converter shown in the embodiments of the present application.

[0064] Figure 2 FIG. is the key waveform of the single-cycle energy control of the resonant high-voltage converter shown in the embodiments of the present application.

[0065] Figure 3 FIG. is a typical simulation waveform of the single-cycle energy control of the resonant high-voltage converter shown in the embodiments of the present application when there is an input disturbance. Detailed Embodiments

[0066] Embodiments of the present application will be described in more detail below with reference to the accompanying drawings. Although the embodiments of the present application are shown in the drawings, it should be understood that the present application can be implemented in various forms and should not be limited by the embodiments set forth herein. On the contrary, these embodiments are provided to make the present application more thorough and complete, and to fully convey the scope of the present application to those skilled in the art.

[0067] It should be understood that although the terms "first", "second", "third", etc. may be used in the present application to describe various information, such information should not be limited to these terms. These terms are only used to distinguish the same type of information from each other. For example, without departing from the scope of the present application, the first information may also be referred to as the second information, and similarly, the second information may also be referred to as the first information. Thus, the features defined with "first" and "second" may explicitly or implicitly include one or more of such features. In the description of the present application, "a plurality" means two or more unless otherwise specifically defined.

[0068] In the description of the present application, it should be understood that the orientation or positional relationship indicated by the terms "length", "width", "upper", "lower", "front", "rear", "left", "right", "vertical", "horizontal", "top", "bottom", "inner", "outer", etc. is based on the orientation or positional relationship shown in the drawings, and is only for the convenience of describing the present application and simplifying the description, rather than indicating or implying that the device or element referred to must have a specific orientation, be constructed and operated in a specific orientation, and thus should not be construed as a limitation of the present application.

[0069] Unless otherwise clearly defined and limited, terms such as "installation", "connection", "linkage", "fixation" shall be understood in a broad sense. For example, it may be a fixed connection, a detachable connection or an integral one; it may be a mechanical connection or an electrical connection; it may be a direct connection or an indirect connection through an intermediate medium, and it may be the internal communication of two components or the interaction relationship between two components. For those of ordinary skill in the art, the specific meanings of the above terms in this application can be understood according to specific circumstances.

[0070] Traditional high-voltage DC conversion consists of a power-frequency transformer with a high step-up ratio and a high-voltage silicon stack, which has problems such as large volume, low efficiency, being greatly affected by power grid fluctuations, and lacking the ability to adjust the output voltage. With the increasing requirements for power quality of high-voltage equipment, switched-mode converters have received extensive attention in high-voltage application scenarios due to advantages such as a wide voltage regulation range, good soft-switching characteristics, small voltage ripple, and high power density. Among them, the phase-shifted full-bridge converter is widely used because of its wide voltage regulation range and high power density, but there is a problem that it is difficult to achieve soft switching of the lagging bridge arm under light load. In contrast, resonant converters are widely used in high-power scenarios due to their excellent soft-switching characteristics. Among them, the LLC resonant converter can achieve zero-voltage turn-on of the primary switch tube and zero-current turn-off of the secondary diode at the same time, and has high efficiency under light load. However, in high-voltage application scenarios, the resonant cavity parameters are easily affected by the output parasitic capacitance of the high-ratio transformer. The LCC resonant converter is widely used in high-voltage output scenarios because it can utilize the output parasitic capacitance of the converter as part of the resonant capacitance.

[0071] In terms of the single-cycle energy control method of resonant converters, the direct frequency control strategy is generally adopted, and the output voltage is controlled by adjusting the resonant cavity gain by controlling the switching frequency, which has problems such as slow dynamic response speed and low bandwidth. In order to meet higher dynamic response requirements, the charge control method is applied to resonant converters. By sampling the voltage across the series resonant capacitor, the input charge within a period is obtained, and then the voltage is adjusted through closed-loop control to make the resonant converter a first-order system, improving the dynamic response performance, but there is a problem of poor light-load stability. At the same time, in order to improve the output voltage stability and reduce the influence of input disturbances on the output voltage stability, the control bandwidth is usually increased to suppress disturbances. However, limited by the low bandwidth of high-voltage sampling technology, it is difficult to meet the suppression of high-frequency disturbances.

[0072] Therefore, the existing single-cycle energy control method of resonant high-voltage DC converters is difficult to meet the requirements of fast voltage regulation during load mutation and stable voltage output under high-frequency input disturbances. In summary, how to improve the dynamic response performance is the technical difficulty of high-voltage DC converters at present.

[0073] Figure 1 Figure (a) is a circuit schematic diagram of the main circuit of the resonant high-voltage converter shown in the embodiment of the present application.

[0074] Figure 1 Figure (b) is a schematic circuit diagram of the control circuit of the resonant high-voltage converter shown in the embodiment of the present application.

[0075] See Figures 1-3 , the first aspect of the present application provides a resonant high-voltage converter, including:

[0076] An LCC resonant cavity circuit, having a first state and a second state;

[0077] A full-bridge inverter circuit, the input end of the full-bridge inverter circuit is electrically connected to the LCC resonant cavity circuit. When the LCC resonant cavity circuit is in the first state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the forward direction. When the LCC resonant cavity circuit is in the second state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the reverse direction;

[0078] An energy control inner loop circuit, having an integrator and a multiplier, for sampling the input voltage of the full-bridge inverter circuit to obtain a first voltage and sampling the input current of the full-bridge inverter circuit to obtain a first current. After multiplying the first voltage and the first current through the multiplier, the result is input into the integrator for integration to obtain the controlled input energy;

[0079] An output voltage control outer loop circuit, for sampling the voltage output at the output end of the full-bridge inverter circuit to obtain a second voltage, subtracting the second voltage from the reference voltage set value and performing a PID operation to obtain the reference energy;

[0080] A processing circuit, electrically connected to the energy control inner loop circuit and the output voltage control outer loop circuit, for obtaining the controlled input energy and the reference energy, and generating a processing signal when the controlled input energy is greater than or equal to the reference energy; and

[0081] A first monostable flip-flop, electrically connected to the processing circuit and the LCC resonant cavity circuit, for controlling the LCC resonant cavity circuit to flip from the first state to the second state when the processing signal is obtained.

[0082] Resonant high-voltage converter and single-cycle energy control method of the present application. The resonant high-voltage converter includes an LCC resonant cavity circuit, a full-bridge inverter circuit, an energy control inner loop circuit, an output voltage control outer loop circuit, a processing circuit, and a first monostable flip-flop. A first voltage is obtained by sampling the input voltage of the full-bridge inverter circuit, and a first current is obtained by sampling the input current of the full-bridge inverter circuit. The product of the first voltage and the first current is input into an integrator through a multiplier for integration to obtain the controlled input energy. A second voltage is obtained by sampling the voltage output at the output terminal of the full-bridge inverter circuit. After taking the difference between the second voltage and the reference voltage set value and performing PID operation, the reference energy is obtained. When the controlled input energy is greater than or equal to the reference energy, a processing signal is generated. When the first monostable flip-flop obtains the processing signal, the first monostable flip-flop controls the LCC resonant cavity circuit to flip from the first state to the second state. Wherein, when the LCC resonant cavity circuit is in the first state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in a positive manner, and when the LCC resonant cavity circuit is in the second state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in a reverse manner. Thus, it can effectively solve the technical problem of how to improve the dynamic response performance of the resonant high-voltage converter to load mutations and input voltage fluctuations by introducing the input energy information in each period in the control circuit, while reducing the requirement for the input DC capacitor, thereby improving the power density of the whole machine.

[0083] The LCC resonant cavity is composed of a series resonant inductor, a series resonant capacitor, and a parallel resonant capacitor. In the full-bridge inverter circuit of the resonant high-voltage converter of this embodiment, the input energy information in each period is introduced, which improves the dynamic response performance of the resonant high-voltage converter to load mutations and input voltage fluctuations, and helps to reduce the requirement for the input DC capacitor and improve the power density of the whole machine.

[0084] Moreover, the resonant high-voltage converter of this embodiment has a fast dynamic response speed during load mutations and output short circuits, and obtains the controlled input energy through a multiplier and an integrator, avoiding complex calculation processes. At the same time, a first voltage obtained by sampling the input voltage of the full-bridge inverter circuit is introduced into the energy control inner loop circuit, enhancing the output voltage stability during input fluctuations, which is beneficial to reducing the DC bus capacitor and improving the power density of the whole machine.

[0085] In this embodiment, the input voltage of the full-bridge inverter circuit is v in (the first voltage), and the input current is i in (the first current). The sampled values of the voltage and the current are multiplied by a multiplier and then sent to a resetable integrator to obtain the controlled input energy W int of the converter in this period:

[0086]

[0087] Without considering the losses in the intermediate links, the input power is equal to the output power.

[0088] Among them, the outer voltage control loop includes an output voltage sampling link, a difference calculation link, a PID operation link, and a DAC conversion link. After sampling the output voltage and converting it through ADC, the difference is calculated with the control reference voltage, and the PID closed-loop operation is performed on the difference result. After the operation result is converted through DAC, the reference energy W is obtained ref .

[0089] When the converter controls the input energy W in reaches the reference energy W ref , the switching tubes S1 - S4 of the full-bridge inverter circuit are triggered to flip, entering the second half cycle. At the same time, the integrator is cleared, so as to ensure that the energy input to the inverter in each cycle is the set value, and voltage control is achieved under closed-loop control.

[0090] The key waveforms are as shown in the appendix Figure 2 , where, v in is the input DC voltage (the first voltage), i in is the DC-side input current (the first current), W int is the control input energy, W ref is the reference energy, V AB is the square-wave voltage output by the full-bridge circuit, and i r is the resonant current. As can be seen from the figure, in the t3 - t4 interval, both the input current and voltage are greater than zero. At this time, the input energy is greater than zero, and the control input energy rises. At the moment of t4, the control input energy rises to the set energy value. At this time, the switching tubes are triggered to act, and the polarity of voltage V ab flips. Because the resonant current in the t3 - t4 is in the same polarity as the inverter, the switching tubes turned on at this moment are turned on with zero voltage, reducing the switching loss. Moreover, when adjusting the output power, the control input energy can reach the set value within t2 - t4 in a half cycle. Without considering the losses in the intermediate links, the input energy is approximately equal to the output energy, realizing fast power adjustment.

[0091] Figure 3 is the typical simulation waveform when there is a high-frequency disturbance on the DC input side. The DC input voltage is 800VDC, the disturbance component has an amplitude of 50V and a frequency of 100kHz, and the output voltage is 18kVDC. As can be seen from the figure, when there is a high-frequency AC disturbance in the input DC voltage, the inner energy control loop is not affected. When the control input energy reaches the set value, the switching tubes are triggered to flip, and it is still possible to control the output energy within a single cycle, and the output voltage V o (the second voltage) is kept stable through the outer voltage loop.

[0092] In this embodiment, the LCC resonant cavity circuit includes: switching transistors S1, S2, S3, and S4. Among them, switching transistors S1 and S4 form a group, and switching transistors S2 and S3 form a group. Specifically, switching transistor S1 is electrically connected to the positive pole of the DC input circuit and the positive input terminal of the full-bridge inverter circuit, and switching transistor S4 is electrically connected to the negative pole of the DC input circuit and the negative input terminal of the full-bridge inverter circuit. That is, by closing switching transistors S1 and S4, it is the first state of the LCC resonant cavity circuit, which can make the full-bridge inverter circuit work in the positive connection; switching transistor S3 is electrically connected to the positive pole of the DC input circuit and the positive input terminal of the full-bridge inverter circuit, and switching transistor S2 is electrically connected to the negative pole of the DC input circuit and the negative input terminal of the full-bridge inverter circuit. That is, by closing switching transistors S2 and S3, it is the second state of the LCC resonant cavity circuit, which can make the full-bridge inverter circuit work in the reverse connection; among them, switching transistors S1 and S2 can be in series, and switching transistor S3 can be in parallel, switching transistors S3 and S4 are in series, and are in parallel with switching transistor S2. The connection point of the positive input terminal of the full-bridge inverter circuit is on the series circuit of switching transistors S1 and S2, and is located between switching transistors S1 and S2. The connection point of the negative input terminal of the full-bridge inverter circuit is on the series circuit of switching transistors S3 and S4, and is located between switching transistors S3 and S4. When switching transistors S1 and S4 are closed and switching transistors S2 and S3 are open (the first state), the positive current of the DC input circuit enters the positive input terminal of the full-bridge inverter circuit through switching transistor S1, and the negative current of the DC input circuit enters the negative input terminal of the full-bridge inverter circuit through switching transistor S4, thus forming the positive connection of the full-bridge inverter circuit; when switching transistors S2 and S3 are closed and switching transistors S1 and S4 are open (the second state), the positive current of the DC input circuit enters the positive input terminal of the full-bridge inverter circuit through switching transistor S3, and the negative current of the DC input circuit enters the negative input terminal of the full-bridge inverter circuit through switching transistor S2, thus forming the reverse connection of the full-bridge inverter circuit. Thus, the input energy in each period is controlled to adjust the output voltage.

[0093] In this embodiment, the processing circuit can be a specified comparator U7. The energy control inner loop circuit can multiply the first voltage and the first current and then integrate to obtain the control input energy W int , and input the control input energy to the first terminal input of the specified comparator U7. The output voltage control outer loop circuit can subtract the second voltage from the reference voltage setting value and then perform a PID operation to obtain the reference energy W ref , and input the reference energy W ref to the second terminal input of the comparator U7. Compare through the specified comparator U7. When the control input energy W int is greater than or equal to the reference energy Wref In this case, a processing signal is generated, which can be a high-level electrical signal. At the control input energy W int less than the reference energy W ref In this case, the processing signal is not output, that is, the output remains at a low level.

[0094] The first monostable flip-flop is Figure 1 The first monostable flip-flop U2 in Figure 1 can generate a high-level flip signal according to the high-level signal output by the specified comparator U7 of the processing circuit. The flip signal is used to control the flip from the closed state of switch tubes S1 and S4 (the first state) to the closed state of switch tubes S2 and S3, entering the second half cycle, so as to ensure that the energy input to the inverter in each cycle is the set value, and the output voltage is controlled by adjusting the input energy. Among them, switch tubes S1, S2, S3, and S4 can be encapsulated in the flip circuit U1 (such as

[0095] The resonant high-voltage converter in this embodiment performs single-cycle energy control through dual-loop control of a voltage outer loop and an energy inner loop, regulating the input energy in each switching cycle to adjust the output voltage, which can achieve a faster dynamic response speed and is beneficial to better coping with load mutation situations.

[0096] The flip of the drive signal occurs in the rising stage of the input energy. At this time, the resonant cavity voltage and current are in phase. Turning on the switch tube at this moment can achieve zero-voltage switching within the full load range, reducing the switching loss.

[0097] The input energy information is obtained through analog devices such as a multiplier and an integrator. The entire energy control inner loop is implemented by an analog circuit, avoiding complex calculation processes, which is beneficial to improving the control loop bandwidth and reliability.

[0098] The input voltage information is introduced into the control loop, which can help suppress the influence of input disturbances on the output voltage, is beneficial to improving the output voltage stability, and can reduce the DC bus capacitance and improve the overall power density of the machine.

[0099] The input voltage sampling can be directly performed through resistor-capacitor voltage division sampling, and the input current sampling can be directly obtained from the voltage across the sampling resistor. Moreover, the sampling positions of the two are grounded together, eliminating the need for an isolated sampling chip and achieving high-sampling-rate and high-bandwidth sampling.

[0100] In some embodiments, it further includes:

[0101] The DC input circuit is electrically connected to the LCC resonant cavity circuit and is used to supply power to the LCC resonant cavity circuit.

[0102] In this embodiment, the LCC resonant cavity circuit is connected through the DC input circuit, and electric energy is transmitted to the full-bridge inverter circuit through the LCC resonant cavity circuit.

[0103] Specifically: Among them, switch tube S1 and switch tube S4 are a group, and switch tube S2 and switch tube S3 are a group. Specifically, switch tube S1 is electrically connected to the positive pole of the DC input circuit and the positive pole input terminal of the full-bridge inverter circuit, and switch tube S4 is electrically connected to the negative pole of the DC input circuit and the negative pole input terminal of the full-bridge inverter circuit. That is, by closing switch tube S1 and switch tube S4, it is the first state of the LCC resonant cavity circuit, which can make the full-bridge inverter circuit work in the positive connection; switch tube S3 is electrically connected to the positive pole of the DC input circuit and the positive pole input terminal of the full-bridge inverter circuit, and switch tube S2 is electrically connected to the negative pole of the DC input circuit and the negative pole input terminal of the full-bridge inverter circuit. That is, by closing switch tube S2 and switch tube S3, it is the second state of the LCC resonant cavity circuit, which can make the full-bridge inverter circuit work in the reverse connection.

[0104] In some embodiments, it further includes:

[0105] The second monostable flip-flop is electrically connected to the processing circuit and the integrator, and is used to send a clearing signal to the integrator when a processing signal is obtained. After the integrator obtains the clearing signal, the integral therein is cleared.

[0106] In this embodiment, the second monostable flip-flop is Figure 1 The second monostable flip-flop U8 in. The second monostable flip-flop U8 generates a clearing signal, that is, a high-level signal, when the processing circuit, that is, the designated comparator U7, outputs a processing signal, that is, a high level. The second monostable flip-flop U8 inputs the high level into the integrator, thereby realizing clearing the integral in the integrator, so that the integrator enters the integration of the next cycle, enabling the resonant high-voltage converter to work in a continuous cycle working state.

[0107] In some embodiments, it further includes:

[0108] The light-load drive compensation circuit is electrically connected to the processing circuit, the energy control inner-loop circuit and the first monostable flip-flop, and is used to generate a compensation signal and send it to the first monostable flip-flop when the processing signal and the controlled input energy are obtained.

[0109] In this embodiment, the light-load drive compensation circuit can generate a compensation signal and send it to the first monostable flip-flop U2 when obtaining the processing signal and the control input energy, so as to drive the flip signal to control the rapid flipping of the closing of the slave switching transistors S1 and S4 (the first state) to the closing of the switching transistors S2 and S3, realizing maximum power transfer for rapid boost. Thus, it effectively solves the problem that during the process of the resonant high-voltage converter switching from light load to heavy load, the control input energy W int cannot reach the reference energy W within a single cycle ref resulting in the output signal of the specified comparator U7 continuously maintaining a low level and the drive signals of the switching transistors S1-S4 in the flip circuit U1 not flipping.

[0110] The light-load compensation circuit solves the problem that in the process of a resonant converter using energy control switching from light load to heavy load, the energy increment within a single cycle is insufficient, resulting in non-flipping of the modulation signal, and avoids complex ramp compensation.

[0111] In some embodiments, the light-load drive compensation circuit includes:

[0112] A third monostable flip-flop, electrically connected to the processing circuit, for generating a trigger signal when obtaining the processing signal;

[0113] A differentiator, electrically connected to the energy control inner-loop circuit, for obtaining the control input energy and determining the zero-crossing point after the control input energy passes through the differentiator as the peak energy point;

[0114] A first comparator, the first input terminal of the comparator is electrically connected to the differentiator, the second input terminal of the comparator is grounded, and the first comparator is used for generating a square-wave signal when the zero-crossing point after the control input energy passes through the differentiator is the peak energy point;

[0115] An AND gate sub-circuit, electrically connected to the third monostable flip-flop, the first comparator and the first monostable flip-flop, for generating a compensation signal and sending it to the first monostable flip-flop when obtaining the trigger signal and the square-wave signal.

[0116] In this embodiment, the third monostable flip-flop is Figure 1 the third monostable flip-flop U5 in

[0117] The differentiator obtains the control input energy, and generates a peak signal when the zero-crossing point after the control input energy passes through the differentiator is the peak energy point. By sending the peak signal to the first input terminal of the first comparator U6 and grounding the second input terminal of the first comparator U6, a square wave signal is generated when the zero-crossing point after the control input energy passes through the differentiator is the peak energy point; and the square wave signal is input into the second input terminal of the gate circuit U4. When the trigger signal and the square wave signal are obtained, a compensation signal is generated and sent to the first monostable flip-flop. Thereby driving the flip signal to control the rapid flipping of the closure of the switching transistors S1 and S4 (the first state) to the closure of the switching transistors S2 and S3, realizing maximum power transfer and rapid boost.

[0118] Among them, when the energy control inner loop circuit is working normally, the specified comparator U7 generates a low-level narrow pulse signal through the third monostable flip-flop U5, and is disabled through the AND gate circuit U4, and does not drive the light load drive compensation circuit, avoiding the conflict between the energy control inner loop circuit and the light load drive compensation circuit. Thus, it effectively solves the problem that the control input energy W int cannot reach the reference energy W within a single cycle ref resulting in the output signal of the specified comparator U7 continuously maintaining a low level and the drive signals of the switching transistors S1-S4 in the flip circuit U1 not flipping.

[0119] In some embodiments, it further includes:

[0120] An OR gate circuit, electrically connected to the processing circuit, the AND gate circuit and the first monostable flip-flop, is used to generate a first trigger signal and send the first trigger signal to the first monostable flip-flop when the compensation signal is obtained, or generate a second trigger signal and send the second trigger signal to the first monostable flip-flop when the processing signal is obtained.

[0121] In this embodiment, the OR gate circuit is Figure 1 the OR gate circuit U3 in. As long as the OR gate circuit U3 obtains the compensation signal or the processing signal, it can generate the corresponding first trigger signal or second trigger signal. That is to say, through the OR gate circuit U3, the situation of ordinary load mutation or input voltage fluctuation of the resonant high-voltage converter and the situation of the operation state of the resonant high-voltage converter switching from light load to heavy load can be distinguished, avoiding conflict situations.

[0122] In some embodiments, it further includes: a hybrid symmetric voltage-doubling rectifier circuit, electrically connected to the input terminal of the full-bridge inverter circuit, and the second voltage is the output voltage of the hybrid symmetric voltage-doubling rectifier circuit.

[0123] In this embodiment, the hybrid symmetric voltage multiplier rectifier circuit can convert a lower AC voltage into a higher DC voltage.

[0124] In some embodiments, the inner energy control loop circuit includes:

[0125] A first sampler for sampling the input voltage of the full-bridge inverter circuit to obtain a first voltage;

[0126] A second sampler for sampling the input current of the full-bridge inverter circuit to obtain a first current;

[0127] A multiplier electrically connected to the first sampler and the second sampler for multiplying the first voltage and the second voltage to obtain a product value; and

[0128] An integrator electrically connected to the multiplier and the processing circuit for integrating according to the product value to obtain the control input energy and delivering the control input energy to the processing circuit.

[0129] In this embodiment, the first sampler is the Figure 1 first sampler k in i , and the second sampler is the Figure 1 second sampler k in vin . The first voltage and the second voltage are multiplied by the multiplier to obtain a product value, and then the integrator integrates according to the product value to obtain the control input energy and delivers the control input energy to the processing circuit. Among them, the integrator is a resetable integrator.

[0130] The input voltage of the full-bridge inverter circuit is sampled by the first sampler to obtain a first voltage; the input current of the full-bridge inverter circuit is sampled by the second sampler to obtain a first current; the first voltage and the second voltage are multiplied by the multiplier to obtain a product value; and the integrator integrates according to the product value to obtain the control input energy and delivers the control input energy to the processing circuit.

[0131] In some embodiments, the outer output voltage control loop circuit includes:

[0132] A third sampler for sampling the voltage output at the output end of the full-bridge inverter circuit to obtain a second voltage;

[0133] An analog-to-digital converter electrically connected to the third sampler for performing analog-to-digital conversion on the second voltage to obtain the converted second voltage;

[0134] A subtractor, electrically connected to the analog-to-digital converter, is configured to subtract the converted second voltage from a reference voltage set value to obtain a subtracted second voltage;

[0135] A PID feedback unit, electrically connected to the analog-to-digital converter, is configured to perform a PID operation on the subtracted second voltage to obtain a specified reference energy;

[0136] A digital-to-analog converter, electrically connected to the PID feedback unit and the processing circuit, is configured to perform digital-to-analog conversion on the specified reference energy to obtain the reference energy and send the reference energy to the processing circuit.

[0137] In this embodiment, the third sampler is like Figure 1 the third sampler k v0 , the analog-to-digital converter is like Figure 1 the ADC converter circuit Figure 1 , the PID feedback unit is like Figure 1 the PID circuit

[0138] The single-cycle energy control method of the resonant high-voltage converter of the present application includes the resonant high-voltage converter described in any one of the above embodiments. The single-cycle energy control method includes:

[0139] Sampling the input voltage of the full-bridge inverter circuit to obtain a first voltage and sampling the input current of the full-bridge inverter circuit to obtain a first current, multiplying the first voltage and the first current by a multiplier and then inputting the product into an integrator for integration to obtain a controlled input energy;

[0140] Sampling the voltage output at the output end of the full-bridge inverter circuit to obtain a second voltage, subtracting the second voltage from a reference voltage set value and then performing a PID operation to obtain a reference energy;

[0141] Generating a processing signal when the controlled input energy is greater than or equal to the reference energy;

[0142] When the first monostable flip-flop obtains the processing signal, the first monostable flip-flop controls the LCC resonant cavity circuit to flip from the first state to the second state;

[0143] Among them, when the LCC resonant cavity circuit is in the first state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the forward direction, and when the LCC resonant cavity circuit is in the second state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the reverse direction.

[0144] In the transformation method of this embodiment, the input voltage of the full-bridge inverter circuit is sampled to obtain a first voltage, and the input current of the full-bridge inverter circuit is sampled to obtain a first current. After the first voltage and the first current are multiplied by a multiplier, they are input into an integrator for integration to obtain the controlled input energy. The voltage output at the output end of the full-bridge inverter circuit is sampled to obtain a second voltage. After the difference between the second voltage and the reference voltage set value is obtained and subjected to PID operation, the reference energy is obtained. When the controlled input energy is greater than or equal to the reference energy, a processing signal is generated. When the first monostable flip-flop obtains the processing signal, the first monostable flip-flop controls the LCC resonant cavity circuit to flip from the first state to the second state. Among them, when the LCC resonant cavity circuit is in the first state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the forward direction, and when the LCC resonant cavity circuit is in the second state, the LCC resonant cavity circuit is connected to the full-bridge inverter circuit in the reverse direction. Thus, it can effectively solve the technical problem of how to improve the dynamic response performance of the resonant high-voltage converter to load mutation and input voltage fluctuation by introducing the input energy information in each period in the control circuit, while reducing the demand for the input DC capacitor, thereby improving the overall power density of the machine.

[0145] Moreover, by introducing the input energy information in each period into the full-bridge inverter circuit of the resonant high-voltage converter in this embodiment, the dynamic response performance of the resonant high-voltage converter to load mutation and input voltage fluctuation is improved, and it helps to reduce the demand for the input DC capacitor and improve the overall power density of the machine.

[0146] In addition, the resonant high-voltage converter in this embodiment has a fast dynamic response speed during load mutation and output short circuit, and the controlled input energy is obtained through a multiplier and an integrator, avoiding complex calculation processes. At the same time, by introducing the sampling of the input voltage of the full-bridge inverter circuit to obtain a first voltage into the inner energy control loop circuit, the stability of the output voltage during input fluctuation is enhanced, which is beneficial to reducing the DC bus capacitor and improving the overall power density of the machine.

[0147] The solutions of the present application have been described in detail above with reference to the accompanying drawings. In the above embodiments, the descriptions of the various embodiments have their own emphases. For parts not described in detail in a certain embodiment, reference may be made to the relevant descriptions of other embodiments. Those skilled in the art should also be aware that the actions and modules involved in the specification are not necessarily essential to the present application. Additionally, it can be understood that the steps in the method embodiments of the present application can be adjusted, combined, and deleted according to actual needs, and the modules in the device embodiments of the present application can be combined, divided, and deleted according to actual needs.

[0148] The various embodiments of the present application have been described above. The above description is exemplary, not exhaustive, and is not limited to the disclosed embodiments. Many modifications and variations are obvious to those of ordinary skill in the art in the technical field without departing from the scope and spirit of the described embodiments. The selection of the terms used herein is intended to best explain the principles of the embodiments, the practical application, or the improvement of the technology in the market, or to enable other ordinary skill in the art in the technical field to understand the embodiments disclosed herein.

Claims

1. A resonant high voltage converter, characterized in that: include: The LCC resonant cavity circuit has a first state and a second state; A full-bridge inverter circuit, wherein an input end of the full-bridge inverter circuit is electrically connected to the LCC resonant cavity circuit, and when the LCC resonant cavity circuit is in a first state, the LCC resonant cavity circuit is positively connected to the full-bridge inverter circuit, and when the LCC resonant cavity circuit is in a second state, the LCC resonant cavity circuit is reversely connected to the full-bridge inverter circuit; An energy control inner loop circuit has an integrator and a multiplier, which is used to sample the input voltage of the full-bridge inverter circuit to obtain a first voltage and sample the input current of the full-bridge inverter circuit to obtain a first current, and multiply the first voltage and the first current by the multiplier and input the product into the integrator for integration to obtain control input energy; An output voltage control outer loop circuit is used to sample the voltage outputted from the output end of the full-bridge inverter circuit to obtain a second voltage, and obtain a reference energy by performing a PID operation after calculating the difference between the second voltage and a reference voltage setting value; a processing circuit, electrically connected to the energy control inner loop circuit and the output voltage control outer loop circuit, for acquiring the control input energy and the reference energy, and generating a processing signal when the control input energy is greater than or equal to the reference energy; as well as a first monostable trigger, electrically connected to the processing circuit and the LCC resonant cavity circuit, and configured to control the LCC resonant cavity circuit to flip from the first state to the second state by the first monostable trigger when the processing signal is acquired; A light-load drive compensation circuit, electrically connected to the processing circuit, the energy control inner loop circuit and the first monostable trigger, for generating a compensation signal and sending it to the first monostable trigger when acquiring the processing signal and the control input energy; The light load drive compensation circuit comprises: a third monostable trigger, electrically connected to the processing circuit, and configured to generate a trigger signal when acquiring the processing signal; a differentiator, electrically connected to the energy control inner loop circuit, for obtaining the control input energy and determining the zero-crossing point of the control input energy after passing through the differentiator as the peak energy point; A first comparator, wherein a first input terminal of the comparator is electrically connected to the differentiator, a second input terminal of the comparator is grounded, and the first comparator is used for generating a square wave signal when a zero-crossing point of the control input energy after passing through the differentiator is a peak energy point; The AND gate subcircuit is electrically connected to the third monostable trigger, the first comparator and the first monostable trigger, and is used to generate a compensation signal and send it to the first monostable trigger after acquiring the trigger signal and the square wave signal.

2. The resonant high-voltage converter according to claim 1, characterized in that: Also includes: A direct current input circuit is electrically connected to the LCC resonant cavity circuit and is used to supply power to the LCC resonant cavity circuit.

3. The resonant high-voltage converter according to claim 2, characterized in that: Also includes: The second monostable trigger is electrically connected to the processing circuit and the integrator, and is used to send a reset signal to the integrator when a processing signal is obtained. The integrator resets the integral therein after obtaining the reset signal.

4. The resonant high-voltage converter according to claim 3, characterized in that: Also includes: An OR gate circuit electrically connects the processing circuit, the AND gate sub-circuit and the first monostable trigger, and is used to generate a first trigger signal and send the first trigger signal to the first monostable trigger when the compensation signal is obtained, or to generate a second trigger signal and send the second trigger signal to the first monostable trigger when the processing signal is obtained.

5. The resonant high-voltage converter according to claim 4, characterized in that: Also includes: A hybrid symmetrical voltage doubler rectifier circuit is electrically connected to the input end of the full-bridge inverter circuit, and the second voltage is the output voltage of the hybrid symmetrical voltage doubler rectifier circuit.

6. The resonant high-voltage converter according to claim 5, characterized in that: The energy control inner loop circuit comprises: A first sampler, used for sampling an input voltage of the full-bridge inverter circuit to obtain a first voltage; A second sampler, used for sampling the input current of the full-bridge inverter circuit to obtain a first current; a multiplier, electrically connected to the first sampler and the second sampler, and configured to multiply the first voltage and the second voltage to obtain a product value; and An integrator is electrically connected to the multiplier and the processing circuit, and is used to integrate according to the product value to obtain the control input energy and transmit the control input energy to the processing circuit.

7. The resonant high-voltage converter according to claim 6, characterized in that: The output voltage control outer loop circuit comprises: A third sampler, used for sampling the voltage outputted by the output terminal of the full-bridge inverter circuit to obtain a second voltage; an analog-to-digital converter, electrically connected to the third sampler, and configured to perform analog-to-digital conversion on the second voltage to obtain a converted second voltage; A difference finder, electrically connected to the analog-to-digital converter, and used to find the difference between the converted second voltage and a reference voltage setting value to obtain a second voltage after the difference is found; A PID feedback device, electrically connected to the analog-to-digital converter, and used for performing a PID operation on the second voltage after the difference is calculated to obtain a specified reference energy; A digital-to-analog converter is electrically connected to the PID feedback device and the processing circuit, and is used to perform digital-to-analog conversion on the specified reference energy to obtain the reference energy and send the reference energy to the processing circuit.

8. A single-cycle energy control method for a resonant high-voltage converter, characterized in that: Comprising the resonant high-voltage converter according to any one of claims 1 to 7, the single-cycle energy control method comprises: Sampling the input voltage of the full-bridge inverter circuit to obtain a first voltage and sampling the input current of the full-bridge inverter circuit to obtain a first current, multiplying the first voltage and the first current by a multiplier and inputting the product into an integrator for integration to obtain control input energy; Sampling the voltage outputted from the output end of the full-bridge inverter circuit to obtain a second voltage, calculating the difference between the second voltage and a reference voltage setting value and performing PID operation to obtain a reference energy; generating a processing signal when the control input energy is greater than or equal to the reference energy; In the case where the first monostable trigger acquires the processing signal, the first monostable trigger controls the LCC resonant cavity circuit to flip from the first state to the second state; Wherein, when the LCC resonant cavity circuit is in a first state, the LCC resonant cavity circuit is positively connected to the full-bridge inverter circuit, and when the LCC resonant cavity circuit is in a second state, the LCC resonant cavity circuit is reversely connected to the full-bridge inverter circuit.

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