Power control method of strong coupling emission array system

Abstract

The invention discloses a power control method of a strong coupling emission array system, which is used for coping with instability and uncertainty phenomena in a system power increasing process. According to the method, the power adjustment process is divided into a plurality of stages, the target power of the first stage is the safe power of the transmitter capable of working under the total reflection condition, and after the target of the first stage is completed, array element phase adjustment is carried out according to beam pointing. In the power adjustment process of each stage, the amplitude of the uncertainty of the system state is reduced by controlling the gain change step pitch, the iteration step number and the error tolerance, the system is prevented from entering the oscillation state, and the uncertainty of the final state of the system is effectively eliminated. The method is low in complexity, easy in engineering implementation, stable in power control process, high in speed and particularly suitable for a large-scale strong coupling emission array system.

Description

Technical Field

[0001] The present invention belongs to the technical field of short-wave high-power transmission, and particularly relates to a power control method for a strongly coupled transmitting array system. Background Art

[0002] Today, with the rapid development of radio frequency wireless technology, the application requirements for high speed and large bandwidth are gradually pushing the frequency of wireless carriers towards the THz band. However, high-frequency (or short-wave) radio still occupies an irreplaceable position due to its unique propagation characteristics. With the reflection or waveguide effect of the ionosphere, short-wave radio waves can achieve global propagation without relays, and it is the only means of over-the-horizon emergency backup communication.

[0003] For high-power transmitters in communication transmission, solid-state power amplifiers (hereinafter referred to as solid-state power amplifiers for short) are currently mainly used to increase the transmission power. Compared with early vacuum devices, solid-state power amplifiers have the advantages of good reliability, large bandwidth, and the ability to achieve multi-target and frequency-hopping jamming. However, the output power of a single device is relatively low, and a multi-stage power combining method needs to be used to achieve high-power output. The greater the output power, the more synthesis stages are required, the greater the power loss, and the lower the overall efficiency. To further increase the transmission power, existing technical solutions use the method of array space power combining, which consists of several antennas and transmitters to form an array, and uses the coherent superposition of the space radiation waves of each antenna to achieve space power combining. Theoretically, the equivalent radiation power of an array composed of M array elements is M 2 times that of a single array element, with an additional M-fold synthesis gain. In addition, space synthesis also has the advantages of no synthesis loss, low power capacity requirements for antennas and combiners, and the ability to quickly and flexibly adjust the beam direction using phased methods, which is particularly suitable for the generation and directional delivery of ultra-large radiation power.

[0004] On the other hand, due to the relatively long wavelength of short waves (the wavelength of 2 MHz reaches 150 m), restricted by the deployment space, the spacing between array element antennas may be small (for example, less than 1 / 3 wavelength), resulting in a strong mutual coupling effect between the array elements; the system has a wide operating bandwidth (close to four octaves), and it is difficult to optimize the standing wave ratio and isolation at the same time, and the indicators are not as good as those of narrow-band arrays. As a result, the array element transmitters may face extremely poor load mismatch conditions when working, and this mismatch is not only the effect of the reflection of a single array element antenna itself, but also includes the contribution of the coupled waves generated by the space coupling of other array elements during transmission. Therefore, the equivalent load of an array element transmitter will be affected by other transmitters.

[0005] In summary, the existing technology cannot meet the power control requirements of a strongly coupled transmitting array system, and it is necessary to design a power control algorithm that can avoid the internal uncertainties of the system and quickly and stably achieve the power control requirements in a large bandwidth and full beam direction. Summary of the Invention

[0006] The present invention mainly solves the problem of the adverse effects of the strong coupling effect of the short-wave spatial power synthesis array on the element transmitter, and discloses a power control method for a strong coupling transmitting array system.

[0007] In the first aspect of the embodiment of the present invention, a power control method for a strong coupling transmitting array system is disclosed, including:

[0008] S1, determining the safe power value P at which the element transmitter in the transmitting array system can operate in total reflection s ;

[0009] S2, setting the target power of the element transmitters in N stages as:

[0010]

[0011] where P f is the transmission power that each element transmitter finally needs to reach, P n is the transmission target power value of the element transmitter in the intermediate stage, P t (n) represents the target power value of the element transmitter at stage count n, P f >P s ; P n satisfies P s <P n <P f ; N is the total number of stages, and N is a natural number;

[0012] S3, performing power control on the element transmitters based on the safe power value for total reflection operation and the target power of the element transmitters.

[0013] The performing power control on the element transmitters based on the safe power value for total reflection operation and the target power of the element transmitters includes:

[0014] S31, setting the phase of the excitation signal of each element transmitter to 0°, and setting the radio frequency amplification link gain G p of each element transmitter as the initial value G 0 , setting the stage count n = 1, and obtaining the output power P out of the element transmitter;

[0015] S32, setting the target power value P nt =P t (n) of stage count n, and iteratively adjusting the radio frequency amplification link gain G p based on the difference between the output power P out of the element transmitter and P nt , until |P out -P nt< dP, where dP is a preset power error tolerance;

[0016] S33, determine whether the stage count n satisfies n = 1 or n = N to obtain a first discrimination result;

[0017] If the first discrimination result is yes, obtain the array beam pointing information, and based on the array beam pointing information, set the phases of the excitation signals of each array element, and execute S34;

[0018] If the first discrimination result is no, execute S34;

[0019] S34, update the stage count n ← n + 1. If n ≤ N, execute S32. Otherwise, exit the power control process, no longer adjust the RF link gain of the transmitter, and the power control process ends.

[0020] The target power value P of the set stage count n nt = P t (n), based on the output power P of the array element transmitter out and P nt difference, iteratively adjust the RF amplification link gain G p , until |P out - P nt | < dP, including:

[0021] S321, set the target power value P of the stage count n nt = P t (n), set the counter value counter = 0;

[0022] S322, determine whether counter > MaxSteps holds to obtain a second discrimination result, where MaxSteps is a preset maximum power adjustment step number;

[0023] If the second discrimination result is yes, give a power adjustment failure flag and execute step S33; otherwise, execute S323;

[0024] S323, obtain the output power P of the array element transmitter out ;

[0025] S324, determine whether |P out - P nt | < dP holds to obtain a third discrimination result;

[0026] If the third discrimination result is yes, execute step S33; otherwise, calculate the power decibel difference Perform gain adjustment calculation processing on the power decibel difference to obtain a gain adjustment amount dG;

[0027] S325, update and calculate the radio frequency link gain G p The update calculation process is expressed as G p ←G p -dG; increment the counter value by 1, i.e., counter←counter + 1; return to step S322.

[0028] The expression for the gain adjustment calculation process is:

[0029]

[0030] where G step is the preset maximum gain adjustment step.

[0031] The said S323 includes:

[0032] Obtain the output power P out and the reflected power P r ;

[0033] When P out >P s and P r >P rmax the target power value of the revision stage count n P rmax is the maximum reflected power that the array element transmitter can withstand.

[0034] The said S323 includes:

[0035] Obtain the output power P out and the reflected power P r ;

[0036] When P out >P s calculate the load standing wave ratio of the array element transmitter Judge whether ρ is greater than the maximum load standing wave ratio ρ max that the transmitter can withstand, to obtain the fourth discrimination result;

[0037] If the fourth discrimination result is yes, turn off the radio frequency output of the transmitter, give out a transmitter over standing wave warning flag, and end the power control process;

[0038] If the fourth discrimination result is no, judge whether P r >P rmax holds, to obtain the fifth discrimination result; if the fifth discrimination result is yes, revise the target power value of the stage count n where P rmax is the maximum reflected power that the transmitter can withstand.

[0039] The said S33 includes:

[0040] S331. Determine whether the stage count n satisfies n = 1 or n = N to obtain a first discrimination result; if the first discrimination result is yes, execute S332; if the first discrimination result is no, execute S34;

[0041] S332. Obtain the array beam pointing information, and determine the target phases of the corresponding M element transmitters according to the array beam pointing information respectively represent the target phases of element transmitter 1 to element transmitter M, and the target phases of element transmitter 2 to element transmitter M are obtained with reference to the target phase of element transmitter 1, which is relative to the deviation, Set the phase adjustment step count value i = 0; M is the total number of element transmitters;

[0042] S333. Collect the complex envelopes of the output signals of each element transmitter, and obtain the phases of the output signals of element transmitters 2 to M with reference to the phase of the output signal of element transmitter 1. The phases of the output signals of element transmitters 2 to M are respectively α 2 , …… α M ;

[0043] S334. Calculate the phase deviations of element transmitters 2 to M m = 2, …, M, Δφ m , α m are respectively the phase deviation, the phase of the output signal, and the target phase of element transmitter m; search for the maximum value Δφ of the absolute value of the phase deviation max = max{|Δφ m |, m = 2, …, M};

[0044] Judge whether Δφ max is less than the preset phase error tolerance to obtain a fifth discrimination result; if the fifth discrimination result is yes, execute step S34, otherwise, execute step S335;

[0045] S335. Judge whether the current phase adjustment step count value i is less than the preset maximum adjustment step N F , that is, i < N F , to obtain a sixth discrimination result;

[0046] If the sixth discrimination result is yes, the M - 1 phase deviation amounts λΔφ m, for m = 2, …, M, are respectively added to the corresponding excitation signals of the array element transmitters 2 to M, where 0 < λ < 1 and λ is a preset real factor. Update i as i = i + 1, and return to step S333; if the sixth discrimination result is negative, give a phase adjustment failure flag and end the power control process.

[0047] Collecting the complex envelopes of the output signals of each array element transmitter and obtaining the phases of the output signals of the array element transmitters 2 to M with the phase of the output signal of the array element transmitter 1 as a reference includes:

[0048] Collecting the complex envelopes of the output signals of each array element transmitter; x m (k) represents the complex envelope value of the output signal of the array element transmitter m at the time of kT s where T s is the sampling period, m = 1, 2, ……, m is the array element number, and k = 1, 2, ……, J, where k is the time domain sampling point number;

[0049] Using the first phase calculation model, performing calculation processing on the complex envelopes of the output signals of each array element transmitter to obtain the phase of the output signal of the array element transmitter m relative to the output signal of the array element transmitter 1.

[0050] The expression of the first phase calculation model is:

[0051]

[0052] In the formula, arg{·} is to take the phase angle, and L represents the number of k that satisfies |x 1 (k)| = 0.

[0053] Collecting the complex envelopes of the output signals of each array element transmitter and obtaining the phases of the output signals of the array element transmitters 2 to M with the phase of the output signal of the array element transmitter 1 as a reference includes:

[0054] Collecting the complex envelopes of the output signals of each array element transmitter; x m (k) represents the complex envelope value of the output signal of the array element transmitter m at the time of kT s where T s is the sampling period, m = 1, 2, ……, M is the array element number, and k = 1, 2, ……, K, where k is the time domain sampling point number;

[0055] Calculating the phase of the m-th array element transmitter relative to the 1st array element transmitter, and the calculation expression:

[0056]

[0057] In the formula, arg{·} is to take the phase angle, x 1 *(k) is x 1 The conjugate of (k).

[0058] In the second aspect of the present invention, a power control device for a strongly coupled emission array system is disclosed. The device includes:

[0059] A memory storing executable program code;

[0060] A processor coupled to the memory;

[0061] The processor calls the executable program code stored in the memory to execute the power control method of the strongly coupled emission array system described above.

[0062] In the third aspect of the present invention, a computer-readable storage medium is disclosed. The computer-readable storage medium stores computer instructions, which are used to execute the power control method of the strongly coupled emission array system when called by a computer.

[0063] In the fourth aspect of the present invention, an information data processing terminal is disclosed. The information data processing terminal is used to implement the power control method of the strongly coupled emission array system described above.

[0064] The beneficial effects of the present invention are as follows:

[0065] The present invention adopts a method of gradually increasing the power to reduce the amplitude of the change in the system power state, so as to reduce the uncertainty of the system state; in the first step, the target power P t (1) is the safe power value P at which the transmitter can work in total reflection s . After completing the first step, phase adjustment is then performed, which avoids the safety impact on the transmitter power amplifier caused by the drastic change in the equivalent load condition due to phase change, and also avoids the out-of-control of the power control process due to the drastic change in the state; in each step of iterative approximation, the maximum gain adjustment step G step is set, and reasonably restricting G step can effectively control the oscillation range of the system state; by reasonably setting the power error tolerance dP and the number of iterative steps, it effectively avoids the over-long control process or entering the oscillation state, ensures that the power setting converges quickly and stably to a determined state, and ensures the stability and safety of the entire system. BRIEF DESCRIPTION OF THE DRAWINGS

[0066] Figure 1 It is a schematic diagram of a 2×2 horizontal log-periodic antenna array;

[0067] Figure 2 It is the load standing wave ratio of each of the 4 array element antennas independently;

[0068] Figure 3 It is the coupling coefficient between the array element antennas;

[0069] Figure 4 The equivalent load standing wave ratio of each array element during beam scanning at the 12 MHz frequency point;

[0070] Figure 5 Schematic diagram of a three-element linear array;

[0071] Figure 6 Iteration results at a 3 dB step;

[0072] Figure 7 Iteration results at a 1 dB step;

[0073] Figure 8 Phase diagram trajectories of 3 dB and 1 dB step iterations;

[0074] Figure 9 Iteration results corresponding to different steps;

[0075] Figure 10 Flowchart of an embodiment of the present invention;

[0076] Figure 11 Flowchart of Scheme 1 of an embodiment of the present invention;

[0077] Figure 12 Schematic diagram of the selection of three key parameters in an embodiment of the present invention;

[0078] Figure 13 Phase adjustment flowchart of an embodiment of the present invention;

[0079] Figure 14 Flowchart of Embodiment 2 of the present invention. Detailed implementation manner

[0080] To better understand the content of the present invention, an embodiment is given here.

[0081] Figure 1 Schematic diagram of a 2×2 horizontal log-periodic antenna array; Figure 2 The load standing wave ratio of each of the 4 array element antennas independently; Figure 3 The coupling coefficient between the array element antennas; Figure 4 The equivalent load standing wave ratio of each array element during beam scanning at the 12 MHz frequency point; Figure 5 Schematic diagram of a three-element linear array; Figure 6 Iteration results at a 3 dB step; Figure 7 Iteration results at a 1 dB step; Figure 8 Phase diagram trajectories of 3 dB and 1 dB step iterations; Figure 9 Iteration results corresponding to different steps; Figure 10 Flowchart of an embodiment of the present invention; Figure 11 Flowchart of Scheme 1 of an embodiment of the present invention;Figure 12 Schematic diagram for selecting three key parameters in the embodiments of the present invention; Figure 13 Flow chart of phase adjustment in the embodiments of the present invention; Figure 14 Flow chart of Embodiment 2 of the present invention.

[0082] Figure 1 is a schematic diagram of a 2×2 transmitting array, which includes four horizontally polarized log-periodic antennas 11 to 14 arranged in a square, with an element spacing of 2λ / 5, where λ is the longest operating wavelength. The standing wave ratios of the element antennas 11 to 14 are respectively tested as Figure 2 shown. In most of the operating frequency bands, the standing wave ratio of the single-element antenna is between 1.5 and 2.0, and in a small number of frequency points, it exceeds 2.5. Figure 3 is the coupling coefficient (unit: dB) between the tested pairs of element antennas. Since the antenna system has reciprocity, there are 6 groups of independent coupling coefficients. For example, the "1 2" curve in the figure represents the coupling between antenna 11 and antenna 12. It can be seen from the coupling coefficient that the strongest coupling does not exceed -16 dB. After configuring the element excitation phases according to different beam directions, the equivalent standing wave ratios of each antenna will change significantly. Figure 4 is the equivalent load standing wave ratio of each element antenna when scanning at an azimuth angle from -30° to +30° and an elevation angle from 10° to 60° at a frequency of 12 MHz. Among them, 15 is the equivalent standing wave ratio of element antenna 11, 16 corresponds to antenna 12, 17 corresponds to antenna 13, and 18 corresponds to antenna 14. It can be seen from 18 in the figure that when the azimuth angle is 30°, the equivalent standing wave ratio of antenna 14 reaches above 3.0, and the maximum reaches 3.8, which is significantly different from the case of a single antenna.

[0083] Figures 1 to 4 The coupling degree of the array shown in [] is not particularly strong. For a vertically polarized log-periodic element antenna with a similar configuration, the coupling degree will reach -10 dB, and the equivalent standing wave ratio will be even worse when the elements are simultaneously excited.

[0084] Taking the Figure 5 simplified model shown to demonstrate the inherent uncontrollable characteristics of the power control process. The model includes three groups of elements 21, 22, and 23. The composition and performance of each group of elements are exactly the same. Taking 21 as an example, it includes a variable gain amplifier (VGA) 211, a power amplifier (PA) 212, and an antenna 213. Among them, the gain K1 of the VGA 211 is a variable quantity, and by changing K 1 to adjust the output level A o1 ; the typical state of the power amplifier 212 at the rated output power is at the compression edge or in a slightly compressed state, and its gain G p1 depends on the equivalent load impedance; the total gain G 1 of the RF amplification path composed of the excitation of the two parts of the amplifier is 1 =Kp1 When the input level is A i , the output level satisfies A o1 = G 1 A i = K 1 ·G p1 A i . Similarly, the output levels of array elements 22 and 23 are respectively A o2 = K 2 ·G p2 A i , A o3 = K 3 ·G p3 A i . The coupling coefficients between array element antennas 211, 221, and 231 are C 12 , C 13 , and C 23 .

[0085] Further simplify the model for numerical simulation: assume that the coupling coefficients are all real numbers; array elements 21 and 23 are symmetric about array element 22, that is, C 12 = C 23 ; the voltage amplitude of the power amplifier in the compression state is limited, and the relationship between the gain and the load state can be approximated as where A r is the amplitude of the reflected wave, G 0 is the gain when the load is matched. The above assumptions deviate from the actual system to a certain extent, but do not affect the demonstration of the chaotic characteristics of the power control process.

[0086] According to the mutual coupling relationship of the array element antennas, the output levels of the three array elements satisfy:

[0087]

[0088] Considering the symmetry between array elements 1 and 3, their states should be exactly the same, that is, A o3 = A o1 , K 3 = K 1 , C 12 = C 23 , then the above system of equations is simplified to:

[0089]

[0090] Under the condition that system parameters such as coupling coefficients, input levels, and output target levels are determined, with the VGA gain K 1 , K 2Solving the system of equations formed by equations (1.1) and (1.2) for the unknowns yields a definite system state. However, in an actual strongly coupled array system, the coupling coefficient is uncertain, and the gain model of the power amplifier is far more complex than the above system of equations. Therefore, a definite VGA gain cannot be obtained by solving the equations.

[0091] The method actually used in engineering is to perform successive iterations to approximate the target power. That is, a set of initial VGA gains is first set, and then the VGA gains are adjusted according to the output levels of the current transmitters to gradually approximate the target output value. Through numerical simulation of this process based on the system of equations (1), it is found that the final state of the power adjustment process is related to the maximum step size of the VGA adjusted in each iteration step.

[0092] In the simulation example, the coupling coefficient C 12 = C 23 = 0.3 (corresponding to approximately -10 dB), C 13 = 0.1 (corresponding to -20 dB), A i = 0.1. The target output level A o2 = A o1 = 1. At this time, if the system of equations (1) is directly solved, K 1 = 14, K 2 = 16. When the iterative process is adopted, taking K 1 = 2, K 2 = 2 as the initial values and the iteration step size not exceeding 3 dB, the results are as shown in Figure 6 . It can be seen that after the 5th step, the system enters a periodic oscillation state. The output level of element 1 oscillates alternately between 0.7 and 1.4, and the output level of element 2 oscillates between 0.4 and 1.5, and the set target cannot be reached. Reducing the iteration step size to 1 dB, the iterative process is as shown in Figure 7 . After the 18th step, it still enters a periodic oscillation state. The difference is that the amplitude fluctuation range of element 1 is reduced to between 0.85 and 1.15, and the amplitude fluctuation range of element 2 is reduced to between 0.8 and 1.2. Taking K 1 , K 2 to form a phase plane, the iterative trajectories under the two step size conditions are plotted in Figure 8 . It can be seen that as the iterative steps progress, the iterative processes begin to separate. The process with a 3 dB step size finally oscillates back and forth between points 241 and 242, and the process with a 1 dB step size finally oscillates between points 251 and 252 and cannot converge to the ideal gain values (14, 16). Further increasing the step size of the gain adjustment from small to large, the iterative results under each step size are obtained. In K 1 , K 2The final state of the system is plotted in the phase plane, as shown in Fig. 12(e). The ideal gain value in the figure is 26. The simulated iteration results oscillate back and forth near 26, and as the gain step increases, the amplitude of the oscillation also increases. When the step is taken near 5.867, the iteration results suddenly converge to point 27, and the critical point of this state transition is extremely sensitive to the value of the step. Point 27 is located at K 2 = 0, which has no practical physical meaning and is a mathematical singularity. This result exhibits typical chaotic characteristics.

[0093] The above simulation example is only a three-element system. When the number of array elements increases and the number of interactions increases, this state uncertainty will be further strengthened. Incorrect power control methods will cause the system to enter multiple uncertain results and fail to achieve the set target power.

[0094] The currently commonly used power control method is automatic level control (ALC). Based on the feedback loop, the output power is compared with the target value, and the difference is used for reverse adjustment. Its mechanism is similar to the above simulation process. Based on a similar principle, there is also the PID control method, which jointly determines the negative adjustment amount with the proportional, integral, and differential components of the difference between the output and the target value to obtain the best adjustment speed and stability. None of the above methods have measures to deal with the state uncertainty of strongly coupled systems and are only suitable for the feedback control of single independent devices.

[0095] Among the existing chaotic system control methods, such as OGY, OPF, VFC, etc., the system model and trajectory need to be known in advance, and all variables of the system need to be centrally controlled. This method is not suitable for the short-wave transmitting array system: First, the power amplifier does not have an accurate non-linear model and cannot predict the control trajectory required for description; second, the deployment scale of the system is large, and centralized control involves delays in information exchange; third, the number of array elements is large, the number of control variables is large, the algorithm complexity is high, and it is not easy to be stable; fourth, there are time requirements for the power control process, and complex algorithms cannot meet the requirements of rapid power increase.

[0096] In summary, the existing technologies cannot meet the power control requirements of strongly coupled transmitting systems. It is necessary to design a power control algorithm that can avoid the inherent uncertainty of the system and quickly and stably achieve the power control requirements in a large bandwidth and all beam directions.

[0097] In the first aspect of the embodiment of the present invention, a power control method for a strongly coupled transmitting array system is disclosed, including:

[0098] S1, determining the safe power value P s ,

[0099] S2, setting the target power of the array element transmitters in N stages to:

[0100]

[0101] Among them, P f is the transmission power that each element transmitter finally needs to reach, and P n is the transmission target power value of the element transmitter in the intermediate stage, and P t (n) represents the target power value of the element transmitter at stage count n, and P f > P s ; P n satisfies P s < P n < P f ; N is the total number of stages, N is a natural number, and typical values are taken as 2, 3, 4, etc.;

[0102] S3. Based on the safe power value that can work in total reflection and the target power of the element transmitter, perform power control on the element transmitter.

[0103] The transmission array system includes a plurality of element transmitters.

[0104] Performing power control on the element transmitter based on the safe power value that can work in total reflection and the target power of the element transmitter includes:

[0105] S31. Set the phase of the excitation signal of each element transmitter to 0°, and the radio frequency amplification link gain G p of each element transmitter is the initial value G 0 , let the stage count n = 1, and obtain the output power P out of the element transmitter;

[0106] S32. Set the target power value P nt = P t (n) of stage count n. Based on the difference between the output power P out of the element transmitter and P nt , iteratively adjust the radio frequency amplification link gain G p , until |P oit - P nt | < dP, where dP is a preset power error tolerance, and its value can be 0.5W;

[0107] S33. Determine whether the stage count n satisfies n = 1 or n = N, and obtain a first discrimination result;

[0108] If the first discrimination result is yes, obtain the array beam pointing information. Based on the array beam pointing information, set the phase of the excitation signal of each element, and execute S34;

[0109] If the first discrimination result is negative, execute S34;

[0110] S34, update the stage count n ← n + 1. If n ≤ N, execute S32; otherwise, exit the power control process, no longer adjust the RF link gain of the transmitter, and the power control process ends.

[0111] The target power value P of the set stage count n nt = P t (n), based on the difference between the output power P of the array element transmitter out and P nt , iteratively adjust the RF amplification link gain G p , until |P out - P nt | < dP, including:

[0112] S321, set the target power value P of the stage count n nt = P t (n), set the counter value counter = 0;

[0113] S322, determine whether counter > MaxSteps holds, to obtain the second discrimination result, where MaxSteps is the preset maximum number of power adjustment steps, typically taken as 10 - 20 times;

[0114] If the second discrimination result is positive, give a power adjustment failure flag and execute step S33; otherwise, execute S323;

[0115] S323, obtain the output power P of the array element transmitter out ;

[0116] S324, determine whether |P out - P nt | < dP holds, to obtain the third discrimination result;

[0117] If the third discrimination result is positive, execute step S33; otherwise, calculate the power decibel difference Perform gain adjustment calculation processing on the power decibel difference to obtain the gain adjustment amount dG;

[0118] S325, perform update calculation processing on the RF link gain G p , the expression of the update calculation processing is G p ← G p - dG; increase the counter value by 1, that is, counter ← counter + 1; return to step S322.

[0119] The expression of the gain adjustment calculation processing is:

[0120]

[0121] Among them, G srep is the preset maximum gain adjustment step;

[0122] The S323 further includes:

[0123] Obtain the output power P of the element transmitter out and the reflected power P r ;

[0124] When P out > P s and P r > P rmax at this time, the target power value of the revision stage count n P rma is the maximum reflected power that the element transmitter can withstand.

[0125] The S323 further includes:

[0126] Obtain the output power P of the element transmitter out and the reflected power P r ;

[0127] When P out > P s at this time, calculate the load standing wave ratio of the element transmitter Judge whether ρ is greater than the maximum load standing wave ratio ρ that the transmitter can withstand max , to obtain the fourth discrimination result;

[0128] If the fourth discrimination result is yes, turn off the RF output of the transmitter, give out a transmitter over standing wave warning flag, and end the power control process;

[0129] If the fourth discrimination result is no, judge whether P r > P rmax is established, to obtain the fifth discrimination result; if the fifth discrimination result is yes, the target power value of the revision stage count n In the formula, P rmax is the maximum reflected power that the transmitter can withstand;

[0130] The S33 includes:

[0131] S331. Judge whether the stage count n satisfies n = 1 or n = N, to obtain the first discrimination result; if the first discrimination result is yes, execute S332; if the first discrimination result is no, execute S34;

[0132] S332. Obtain the array beam pointing information, and determine the target phases of the corresponding M element transmitters according to the array beam pointing information. respectively represent the target phases of element transmitter 1 to element transmitter M. The target phases of element transmitter 2 to element transmitter M are obtained with reference to the target phase of element transmitter 1. is the deviation relative to ; Set the phase adjustment step count value i = 0; M is the total number of element transmitters.

[0133] S333. Collect the complex envelopes of the output signals of each element transmitter. With the phase of the output signal of element transmitter 1 as the reference, obtain the phases of the output signals of element transmitters 2 to M. The phases of the output signals of element transmitters 2 to M are respectively α 2 , …… α M ;

[0134] S334. Calculate the phase deviations of element transmitters 2 to M m = 2, …, M, Δφ m , α m are respectively the phase deviation, the phase of the output signal, and the target phase of element transmitter m; Search for the maximum value Δφ of the absolute value of the phase deviation max = max{|Δφ m |, m = 2, …, M};

[0135] Judge whether Δφ max is less than the preset phase error tolerance to obtain the fifth discrimination result; if the fifth discrimination result is yes, execute step S34, otherwise, execute step S335;

[0136] S335. Judge whether the current phase adjustment step count value i is less than the preset maximum adjustment step N F , that is, i < N F , to obtain the sixth discrimination result;

[0137] If the sixth discrimination result is yes, add the phase deviation amount λΔφ m , m = 2, …, M, to the corresponding excitation signals of element transmitters 2 to element transmitter M respectively, where 0 < λ < 1 and λ is a preset real factor, i = i + 1, and return to step S333; if the sixth discrimination result is no, give a phase adjustment failure flag and end the power control process.

[0138] The step of collecting the complex envelopes of the output signals of each element transmitter and obtaining the phases of the output signals of element transmitters 2 to M with the phase of the output signal of element transmitter 1 as the reference includes:

[0139] The complex envelopes of the output signals of each element transmitter are acquired; x m (k) represents the complex envelope value of the output signal of element transmitter m at kT s moment, t s is the sampling period, m = 1, 2, ……, M, is the element number, k = 1, 2, ……, K, k is the time-domain sampling point number;

[0140] Using the first phase calculation model, the complex envelopes of the output signals of each element transmitter are calculated and processed to obtain the phase of the output signal of element transmitter m relative to that of element transmitter 1.

[0141] The expression of the first phase calculation model is:

[0142]

[0143] where arg{·} is to take the phase angle, and L represents the number of k that satisfies |x 1 (k)| = 0.

[0144] The acquisition of the complex envelopes of the output signals of each element transmitter, with the phase of the output signal of element transmitter 1 as the reference, to obtain the phases of the output signals of element transmitters 2 to M includes:

[0145] The complex envelopes of the output signals of each element transmitter are acquired; x m (k) represents the complex envelope value of the output signal of element transmitter m at kT s moment, T s is the sampling period, m = 1, 2, ……, M, is the element number, k = 1, 2, ……, K, k is the time-domain sampling point number;

[0146] The phase of the m-th element transmitter relative to the 1st element transmitter is calculated, and the calculation expression:

[0147]

[0148] where arg{·} is to take the phase angle, x 1 * (k) is the conjugate of x 1 (k).

[0149] The determination of the target phases of the corresponding M elements according to the array beam pointing information can be obtained from the look-up table of the beam pointing of the element transmitter or calculated according to the adaptive beamforming algorithm.

[0150] The maximum number of adjustment steps N F can be 10.

[0151] Further, the step S32 is as follows:

[0152] Set the current step target power value P nt = P t (n), and adjust the RF amplification link gain G through feedback p , and establish a mapping relationship between the power supply voltage of the power amplifier that tracks the change of the input RF envelope according to the input and output RF envelopes of the transmitter, so that the output power P of the transmitter out satisfies |P out - P nt | < dP (dP is the power error tolerance), and the distortion degree between the input and output envelopes reaches the minimum.

[0153] In the second aspect of the implementation of the present invention, a power control method for a strongly coupled transmission array system is disclosed, including:

[0154] To achieve the output power of the array element of P f , the following steps are adopted:

[0155] Step 31: Determine the safe power value P at which the transmitter can work in total reflection s , and set N segments of target power P t (n), n = 1, 2,... N.

[0156] Among them, the safe power value P for total reflection work s mainly depends on the design of the final power amplifier of the transmitter. Based on reasonable circuit schemes and parameter selections, this safe power value can be found. For the power amplifier of the transmitter involved in this embodiment, the safe power value P for total reflection work s can reach 20% - 30% of the rated output power.

[0157] Divide the target power P that the transmitter finally needs to reach f into N segments, and the target power value of each segment is defined as

[0158]

[0159] where P s < P n < P f .

[0160] The advantages of the scheme for achieving the target power in segments here are as follows:

[0161] First of all, achieving the target power in segments can reduce the change range of the power state of each segment of the system, thereby reducing the distribution range of the uncertainty of the power control result.

[0162] Secondly, the array system must adjust the phase according to the beam direction. When the phase changes, it will cause a drastic change in the equivalent load impedance of each element transmitter. During this dynamic process, the transmitter may have to bear the mismatch state of total reflection. Therefore, as an important technical feature of the present invention, the target power at the first end is set to P s , to ensure the safety of the transmitter during the next phase adjustment.

[0163] The number of segments N is related to the final P f , and is also related to the requirement of power control speed.

[0164] One solution in this embodiment is to divide it into two segments, that is, N = 2. At this time, P t (1) = P s , P t (2) = P f . Another solution in this embodiment is to take N = 3, and the segmented target power is taken as P t (1) = P s , P t (2) = 0.6P f . P t (3) = P f .

[0165] Step 32: Set the phase of the excitation signal of each element to 0°, and the initial gain G p = G 0 , and let n = 1.

[0166] This step completes the necessary initialization settings. There is no requirement for the phase of the excitation signal. For simplicity, it is set to 0° in this embodiment. The initial gain G 0 of the transmitter is generally selected according to experience. In this embodiment, it is selected 20 dB lower than the rated design gain value of the transmitter. The variable n is a counter, representing the number of target power segments currently being executed, and the initial value is 1.

[0167] Step 33: Set the current target power P nt = P t (n); Read the current output power P out of the transmitter, and adjust the gain G out of the radio frequency path of the transmitter according to the difference between P nt and P p , until |P ou - P nt | < dP, where dP is the power error tolerance.

[0168] This step makes the output power reach within the error tolerance range of the target power through feedback iteration. Factors such as the gain adjustment step size, power error tolerance, and iteration exit condition in the iteration process determine the final state of the system, or rather, the degree of uncertainty of the final state.

[0169] To effectively control the uncertainty of the iteration result, the first specific solution of this embodiment is as follows Figure 12 shown, including the following steps:

[0170] Step 41: Set the target power value P of the current segment nt = P t (n), and the counter counter = 0;

[0171] Initialize. The counter counter is used to record the number of gain adjustment steps.

[0172] Step 42: Determine whether counter > MaxSteps holds. If it holds, execute Step 43; otherwise, execute Step 44.

[0173] MaxSteps is the maximum number of gain iteration steps, which limits the number of gain adjustments and prevents the system state from entering oscillation.

[0174] Step 43: Give an indication of power adjustment failure and exit the power adjustment process.;

[0175] If the target power tolerance range is not reached within the limited number of times, the current actual transmission power is maintained and the next step is entered to avoid repeated oscillation of the output amplitude.

[0176] Step 44: Read the current output power P of the transmitter out .

[0177] Step 45: Determine whether |P out - P nt | < dP holds. If it holds, exit the power adjustment process; otherwise, execute Step 46.

[0178] Step 46: Calculate the power difference Determine the gain adjustment amount dG from Δ and the maximum gain adjustment step G slep .

[0179] When adjusting the gain of the transmitter, not only will it change its own output power, but it will also affect the output of other transmitters through spatial coupling. The power changes of other transmitters will simultaneously affect this transmitter. Therefore, the size of the gain adjustment directly determines the change trajectory of the system state. As an important feature of the technical solution of the present invention, the adjustment step is restricted. Specifically, the gain adjustment amount dG is calculated according to the following formula

[0180]

[0181] That is, ensure |dG| ≤ G step .

[0182] Step 47: Set the transmitter RF link gain G p = G p - dG; increment the step counter counter = counter + 1; return to step 44.

[0183] In the solution of this embodiment, the maximum number of iteration steps MaxSteps, the maximum gain adjustment step G step and the power error tolerance dP are three important parameters and also important technical features of the present invention. By reasonably setting these three parameters, the uncertainty of the system state can be minimized.

[0184] Take Figure 13 as an example to illustrate the role of the above three parameters in the power adjustment process. Figure 13 Adopt Figure 5 The simulation results of the three-array element model shown in Figure 18 are obtained when the maximum gain step is 2dB. It can be seen that before the 10th step (i.e., the vertical line 51 in the figure), the power change process is basically a monotonically increasing trend. Selecting the maximum number of iteration steps MaxSteps at the 51 position can avoid entering the subsequent oscillation state. The power error tolerance +dP corresponds to Figure 13 the horizontal line 521 in Figure 20, -dP corresponds to the horizontal line 522. Entering the area between 521 and 522 is considered to reach the target power and complete the power control process. Figure 13 In Figure 22, dP is 0.5dB. The elements 1 and 3 meet the power tolerance at 53, and the element 2 meets the requirements at 54. Obviously, the larger dP is, the earlier the iteration process will meet the tolerance requirements and the easier it is to achieve the control target, but the final power deviation will increase.

[0185] The maximum gain step G step is a decisive parameter. The smaller G step is, the smaller the uncertainty A( Figure 13 the 55 in Figure 31) is. However, MaxSteps is also associated with G step , and MaxSteps increases as G step decreases.

[0186] Therefore, the above three parameters need to be determined through experimental debugging in combination with the actual characteristics of the system, the power control speed, and the final accuracy requirements. In the solution of this embodiment, G step = 2dB, MaxSteps = 15, dP = 0.5dB are selected.

[0187] The second solution of this embodiment introduces a protection strategy for excessive reflected power. When the equivalent load of the transmitter is severely mismatched (i.e., overloaded), posing a safety hazard to the power amplifier, the target power is reduced or the RF output is turned off according to the maximum transmit power that can be tolerated. Compared with the first solution, all steps are the same except for step 44. Specifically, step 44 of the second solution is as follows:

[0188] Step 44: Read the output power P of the current transmitter out and the reflected power P r ; when P out > P s , first calculate the load standing wave ratio of the transmitter If ρ is greater than the maximum load standing wave ratio ρ that the transmitter can withstand max , turn off the RF output of the transmitter, give out a transmitter overstanding wave warning flag, and exit this power iteration process; otherwise, if P r > P rmax , then revise the current step target power value where P rmax is the maximum reflected power that the transmitter can withstand. The maximum load standing wave ratio ρ max that the transmitter can withstand satisfies

[0189] Since the transmitter can withstand the full reflection power of P s , the overload protection should be started only when P out > P s . First, calculate the standing wave according to the reflected power. If the standing wave ratio is lower than the protection threshold ρ max , then judge whether the reflected power exceeds the maximum reflected power threshold P rmax . If it is over the limit, reduce the target power according to the overlimit ratio; otherwise, turn off the RF output, give out a warning flag, and terminate the power iteration process.

[0190] To ensure that the protection threshold for turning off the RF is higher than the protection threshold for reducing the power, it is required that ρ max satisfies

[0191] In this embodiment, according to the design of the power amplifier circuit, take P rmax = 0.2P or , P or is the rated output power, and take ρ max = 6.0.

[0192] Now return to Figure 3 the embodiment shown.

[0193] Step 34: Judge whether the current power adjustment stage is the first stage or the Nth stage. If so, execute Step 35; otherwise, execute Step 36.

[0194] Step 35: Read the phase of each array element according to the beam direction and set the phase of the excitation signal of each array element.

[0195] The antenna array design gives the phase configurations of the array elements for different beam directions. Due to the non-linear distortion of the power amplifier, especially after the strong coupling causes serious mismatch of the load, the phase transmission characteristics of the transmitter RF channel change accordingly, and there will be an obvious error between the preset phase and the finally output phase of the transmitter. To ensure the phase accuracy of the array elements, the feedback adjustment scheme is adopted in this embodiment.

[0196] The specific process is as Figure 14 shown. Among them:

[0197] Step 61: Read the phase configurations of each array element according to the beam direction; i = 0.

[0198] Let the phases of M array elements Generally, taking the phase of element 1 as a reference, is the deviation relative to , and i is the phase adjustment step counter.

[0199] Step 62: Collect the complex envelopes of the output signals of the transmitters of each array element, and calculate the relative phases of array elements 2 to M with element 1 as a reference.

[0200] Sample the output RF signal of the transmitter. After analog-to-digital conversion (ADC) and quadrature down-conversion, its baseband complex envelope signal is obtained. Let the sampling period be T s , and the complex envelope sampling sequence of element m is expressed as x m (k), where m = 1, 2,..., M, and k = 1, 2,..., K are the time-domain sampling point numbers, with a total of K sampling points.

[0201] The first phase calculation method in this embodiment: Taking the phase of the transmitter of element 1 as a reference, the phase of the mth element is as follows:

[0202]

[0203] In the formula, arg{·} is to take the phase angle, and L represents the number of points where |x 1 (k)| = 0. That is, the average value of the phases is taken after dividing complex numbers. To perform the division operation, the points where |x 1 (k)| = 0 need to be excluded.

[0204] The second phase calculation method in this embodiment is: Through the least squares method, the following formula is obtained:

[0205]

[0206] In the formula, arg{·} is to take the phase angle, and x 1 * (m) is the conjugate of x 1 (k).

[0207] Step 63: Calculate the deviation Δφ between the relative phase of array elements 2 to M with respect to array element 1 and the configured phase, m and search for the maximum value of the deviation.

[0208] The calculation of the phase deviation is m = 2, …, M, and its maximum value is Δφ max = max{|Δφ m |, m = 2, …, M}.

[0209] Step 64: Determine whether the phase deviation meets the standard. If so, exit the phase setting process; otherwise, execute Step 65. That is, determine whether Δφ max reaches the phase error tolerance. In this embodiment, the phase tolerance can be taken as 5°.

[0210] Step 65: Determine whether i < N F holds, where N F is the maximum number of phase iterations. If so, execute Step 67; otherwise, execute Step 66.

[0211] Step 66: Output the phase adjustment failure flag and exit the power adjustment process.

[0212] Step 67: Modify the phase of the excitation signal of each array element by λφ m (m = 2, …, M), where 0 < λ < 1 is a real number; i = i + 1; return to Step 62.

[0213] When modifying the excitation signal of each array element, it is also necessary to consider that the nonlinear effect may cause phase uncertainty. Therefore, the phase deviation needs to be attenuated by λ times before being corrected into the excitation signal. In this embodiment, λ is taken as 1 / 2 to 1 / 3.

[0214] To detect the output phase of the transmitter, the transmitter needs to provide an output signal with a certain power. As an important technical feature of the present invention, this step is started after the first stage of power adjustment, and the target power of the first stage is set to P s , and the mismatch change caused by the phase adjustment will not cause safety problems or trigger overload protection. After the power adjustment in the Nth stage, in order to ensure the phase accuracy, this step of phase setting is performed again.

[0215] Step 36: Increase the stage number n = n + 1 and prepare to enter the power adjustment of the next stage.

[0216] Step 37: Determine whether n ≤ N holds. If it holds, return to Step 33; otherwise, exit the process and the power control process ends.

[0217] Another embodiment of the present invention is as follows Figure 14As shown, the power control method is implemented on a short-wave transmitter with envelope tracking function. Among them, steps 71 to 77 correspond one by one to steps 31 to 37 of the Figure 13 embodiment shown. Except that step 73 is different from step 33, the other steps are the same. Only the differences are described as follows:

[0218] Step 73: Set the current step target power value P nt = P t (n). Adjust the gain G of the RF amplification link through feedback, p and establish a mapping relationship between the power supply voltage of the power amplifier that tracks the change of the input RF envelope according to the input and output RF envelopes of the transmitter, so that the output power P of the transmitter out satisfies |P out - P nt | < dP (dP is the power error tolerance), and the distortion degree between the input and output envelopes reaches the minimum.

[0219] For the envelope tracking transmitter adopted in this embodiment, the power supply voltage of its power amplifier changes with the input signal envelope. To ensure that the output signal envelope of the power amplifier reaches the minimum distortion degree, it is necessary to adjust the mapping relationship between the input envelope and the power supply voltage based on the principle of minimum distortion. While ensuring the minimum distortion degree, the output power P out also needs to reach the target value P nt within the tolerance range.

[0220] The power control method of the strongly coupled transmitter array system of the present invention reduces the system uncertainty amplitude through a phased power increase scheme. The first stage sets a safe output power that cannot work in total reflection. After the first stage, the phase of the array elements is adjusted, effectively avoiding the overload of the transmitter caused by strong coupling. By controlling the gain adjustment step size, the maximum number of iteration steps, and the power error tolerance in each stage, the system is prevented from entering oscillation, the uncertainty is eliminated, the algorithm complexity is low, the engineering implementation is easy, and the power control effect is fast and stable.

[0221] The above are only the embodiments of the present invention and are not used to limit the present invention. For those skilled in the art, various changes and modifications can be made to the present invention. Any modification, equivalent replacement, improvement, etc. made within the spirit and principle of the present invention shall be included within the scope of the claims of the present invention.

Claims

1. A power control method for a strongly coupled transmitting array system, characterized in that: include: S1, determine the safe power value P of the element transmitter in the transmitting array system for full reflection operation s ; S2, set the target power of the array element transmitter in N stages to: Among them, P f is the transmission power that each array element transmitter needs to achieve in the end, P n is the target power value of the array element transmitter in the intermediate stage, P t (n) represents the target power value of the array element transmitter at stage count n, P f >P s ;P n Satisfy P s <P n <P f ; N is the total number of stages, N is a natural number; S3, performing power control on the array element transmitter based on the safe power value for full reflection operation and the target power of the array element transmitter.

2. The power control method of the strongly coupled transmit array system according to claim 1, characterized in that: The performing power control on the array element transmitter based on the safe power value for full reflection operation and the target power of the array element transmitter comprises: S31, set the phase of the excitation signal of each array element transmitter to 0°, and the RF amplification link gain G of each array element transmitter p Assume that G0 is the initial value, set the stage count n = 1, and obtain the output power P of the array element transmitter out ; S32, set the target power value P of the stage count n nt = P t (n), based on the output power P of the array element transmitter out and P nt of the difference, iteratively adjust the RF amplification link gain G p , until |P out - P nt | < dP, where dP is the preset power error tolerance; S33, determining whether the stage count n satisfies n=1 or n=N, and obtaining a first determination result; If the first determination result is yes, acquiring array beam pointing information, setting the phase of the excitation signal of each array element based on the array beam pointing information, and executing S34; If the first determination result is no, executing S34; S34, update the phase count n←n+1, if n≤N, execute S32, otherwise, exit the power control process, no longer adjust the transmitter's RF link gain, and the power control process ends.

3. The power control method of the strongly coupled transmit array system as claimed in claim 2, characterized in that: The target power value P for setting the stage count n nt = P t (n), based on the output power P of the array element transmitter out and P nt The difference of, iteratively adjust the RF amplification link gain G p , until |P out - P nt | < dP, including: S321, setting the target power value P of stage count n nt =P t (n), set the counter value counter = 0; S322, determining whether counter>MaxSteps is established, and obtaining a second determination result, wherein MaxSteps is a preset maximum power adjustment step number; If the second determination result is yes, a power adjustment failure flag is given and step S33 is executed; otherwise, step S323 is executed; S323, obtaining the output power P of the array element transmitter out ; S324, determine |P out -P nt Determine whether |<dP holds to obtain the third discrimination result; If the third determination result is yes, execute step S33; otherwise, calculate the power decibel difference Performing gain adjustment calculation processing on the power decibel difference to obtain a gain adjustment amount dG; S325, for RF link gain G p Perform update calculation processing, the expression of the update calculation processing is G p ←G p -dG; increase the counter value by 1, that is, counter←counter+1; return to step S322.

4. The power control method of the strongly coupled transmit array system as claimed in claim 3, characterized in that: The expression of the gain adjustment calculation process is: Among them, G step Adjust the step size for the preset maximum gain.

5. The power control method of the strongly coupled transmit array system as claimed in claim 4, characterized in that: The S323 includes: Get the output power P of the array element transmitter out and reflected power P r ; When P out >P s And P r >P rmax When the target power value of the revision phase count n is P rmax It is the maximum reflected power that the array element transmitter can withstand.

6. The power control method of the strongly coupled transmit array system as claimed in claim 4, characterized in that: The S323 includes: Get the output power P of the array element transmitter out and reflected power P r ; When P out >P s When , the load standing wave ratio of the array element transmitter is calculated Determine whether ρ is greater than the maximum load standing wave ratio ρ that the transmitter can withstand max , and obtain the fourth discrimination result; If the fourth determination result is yes, turn off the radio frequency output of the transmitter, give a standing wave warning sign of the transmitter, and end the power control process; If the fourth determination result is no, determine P r >P rmax Is it established, get the fifth judgment result; if the fifth judgment result is yes, revise the target power value of the stage count n Where P rmax It is the maximum reflected power that the transmitter can withstand.

7. The power control method of the strongly coupled transmit array system as claimed in claim 6, characterized in that: The S33 comprises: S331, determine whether the stage count n satisfies n=1 or n=N, and obtain a first determination result; if the first determination result is yes, execute S332; if the first determination result is no, execute S34; S332, obtaining array beam pointing information, and determining the target phases of the corresponding M array element transmitters according to the array beam pointing information They respectively represent the target phases of array element transmitter 1 to array element transmitter M. The target phases of array element transmitter 2 to array element transmitter M are obtained with reference to the target phase of array element transmitter 1. is relative The deviation Set the phase adjustment step count value i=0; M is the total number of array element transmitters; S333, collecting the complex envelope of the output signal of each array element transmitter, taking the phase of the output signal of array element transmitter 1 as a reference, obtaining the phase of the output signal of array element transmitters 2 to M, wherein the phases of the output signals of array element transmitters 2 to M are α2, ..., α M ; S334, calculate the phase deviation of array element transmitters 2 to M m=2,…,M,Δφ m , α m are the phase deviation of the array element transmitter m, the phase of the output signal and the target phase respectively; the maximum value of the absolute value of the phase deviation Δφ is obtained by searching max =max{|Δφ m |, m = 2, ..., M}; Determine Δφ max is less than a preset phase error tolerance, obtaining a fifth determination result; if the fifth determination result is yes, executing step S34, otherwise, executing step S335; S335: Determine whether the current phase adjustment step count value i is less than the preset maximum adjustment step number N F , i.e. i <N F , and obtain the sixth discrimination result; If the sixth judgment result is yes, set M-1 phase deviations λΔφ m ,m=2,…,M, are added to the corresponding excitation signals from array element transmitter 2 to array element transmitter M respectively, where 0<λ<1, λ is a preset real number factor, i is updated to i=i+1, and the process returns to step S333; if the result of the sixth judgment is no, a phase adjustment failure flag is given and the power control process ends.

8. The power control method of the strongly coupled transmit array system as claimed in claim 7, characterized in that: The step of collecting the complex envelope of the output signal of each array element transmitter and obtaining the phase of the output signal of array element transmitters 2 to M with the phase of the output signal of array element transmitter 1 as a reference includes: Collect the complex envelope of the output signal of each array element transmitter; m (k) represents the array transmitter m at kT s The complex envelope value of the output signal at time T s is the sampling period, m=1,2,……,M, is the array element number, k=1,2,……,K, k is the time domain sampling point number; The complex envelopes of the output signals of the array element transmitters are calculated and processed by using the first phase calculation model to obtain the phase of the output signal of the array element transmitter m relative to the array element transmitter 1.

9. The power control method of the strongly coupled transmit array system as claimed in claim 8, characterized in that: The expression of the first phase calculation model is: Wherein, arg{·} is the phase angle, and L represents the number of k satisfying |x1(k)|=0.

10. The power control method of the strongly coupled transmit array system as claimed in claim 7, characterized in that: The step of collecting the complex envelope of the output signal of each array element transmitter and obtaining the phase of the output signal of array element transmitters 2 to M with the phase of the output signal of array element transmitter 1 as a reference includes: Collect the complex envelope of the output signal of each array element transmitter; m (k) represents the array transmitter m at kT s The complex envelope value of the output signal at time T s is the sampling period, m=1,2,……,M, is the array element number, k=1,2,……,K, k is the time domain sampling point number; The phase of the mth array element transmitter relative to the 1st array element transmitter is calculated, and the calculation expression is: In the formula, arg{·} is the phase angle, x1 * (k) is the conjugate of x1(k).

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