A high-gain dual-polarized parabolic antenna system and its performance preservation method

Abstract

This invention relates to a high-gain dual-polarized parabolic antenna system and its performance preservation method. The system includes: a parabolic reflector; a feed source disposed at the focal or near-focal region of the parabolic reflector; the feed source includes a printed circuit board (PCB) on which metal oscillator elements are formed by etching; the metal oscillator elements include at least two sets of orthogonally arranged oscillators, forming radiation in two orthogonal polarization directions; each oscillator element integrates a low-frequency radiating section for a first frequency band and a high-frequency radiating section for a second frequency band, the first and second frequency bands corresponding to the 900MHz and 1800MHz frequency bands, respectively; the feed source radiates dual-polarized electromagnetic waves through the metal oscillator elements, and the electromagnetic waves are reflected by the parabolic reflector to form a high-gain directional beam. This invention achieves a compact structure and low-cost manufacturing while significantly improving the electrical performance of the antenna over a wide bandwidth, providing an efficient and flexible solution for modern wireless communication.

Description

Technical Field

[0001] This invention relates to the field of antenna system equipment technology, and in particular to a high-gain dual-polarized parabolic antenna system and a method for maintaining its performance. Background Technology

[0002] With the continuous evolution of 4G and future 5G mobile communication technologies, wireless communication systems are placing higher demands on antenna performance. To effectively improve channel capacity and spectrum utilization, MIMO (Multiple-Input Multiple-Output) technology has become the mainstream deployment solution, requiring antennas to have explicit dual-polarization capabilities. Simultaneously, in specific scenarios such as emergency communications, temporary base station deployment for large-scale events, and wide-area coverage in rural areas, antennas need to possess high gain and strong directivity to quickly establish stable and reliable wireless connections. Parabolic antennas, with their inherent advantages of achieving high gain and narrow beamwidth, have become a common choice in these application scenarios.

[0003] In practical deployments, considering the compatibility of different network standards (such as 2G / 3G / 4G) and the effective utilization of spectrum resources, antennas typically need to cover a wide frequency band or simultaneously support multiple widely separated frequency bands, such as 900MHz and 1800MHz. Existing technologies typically employ increasing the diameter of parabolic reflectors to achieve high gain of 15-25 dBi, using reflector shaping or special feed design techniques to reduce sidelobe levels to below -20 dB, and achieving low voltage standing wave ratios (VSWR ≤ 1.7) within the required frequency bands through gradient feed structures or complex impedance matching networks. However, existing technologies still face significant challenges in designing feeds that simultaneously meet the requirements of high gain, dual polarization, dual frequency bands (especially 900MHz and 1800MHz), and are compact, low-cost, and easy to mass-produce.

[0004] 1. The Challenge of Dual-Band Integration and Performance Balancing: Achieving good resonance characteristics and impedance matching simultaneously in a single feed structure for the 900MHz and 1800MHz frequency bands, which are nearly harmonics apart, is a complex task. Existing PCB feeds, if intended to cover both bands simultaneously, often require multi-layer PCBs or complex coupling structures, leading to increased feed size, structural complexity, and the potential for undesirable mutual coupling between radiating elements of different frequency bands, affecting the performance of each band.

[0005] 2. Insufficient Integration of Dual Polarization and Dual Frequency: Traditional dual-polarization feed designs achieve this through the orthogonal arrangement of two independent single-polarization feeds or complex orthogonal mode couplers. When further integrating dual-frequency functionality is required, existing technologies often struggle to maintain a compact structure while ensuring high polarization isolation between the two orthogonal polarization ports in both operating frequency bands. Integrating two operating frequency bands and two orthogonal polarization radiating elements on a PCB using a planar etching structure, while ensuring low mutual coupling and excellent performance within their respective frequency bands, remains a persistent but unresolved technical challenge in antenna design.

[0006] 3. Manufacturing process complexity and cost control: Existing dual-frequency dual-polarization feed sources, if using non-PCB processes or complex multi-layer PCB designs, will increase manufacturing complexity, material costs, and production cycles, which is not conducive to large-scale, low-cost deployment. How to efficiently achieve high-performance dual-frequency dual-polarization feed sources through a planar etching structure of a single layer or a few layers of PCB is a technical bottleneck that urgently needs to be solved.

[0007] Given the shortcomings of the existing technology, there is an urgent need for an innovative solution that can provide a parabolic antenna feed and antenna based on a PCB-etched metal vibrator, which has a relatively simple structure, is easy to manufacture, and has good impedance matching, high gain and dual polarization characteristics in both the 900MHz and 1800MHz frequency bands. Summary of the Invention

[0008] To address the problems of existing technologies as much as possible, this invention provides a high-gain dual-polarized parabolic antenna system. By integrating a dual-band (900MHz and 1800MHz) and dual-polarized metal vibrator unit on a single printed circuit board (PCB), it helps overcome the challenges of existing dual-band dual-polarized feed sources in terms of structural complexity, manufacturing difficulty, good impedance matching over a wide bandwidth, and high polarization isolation. This provides a high-performance and easy-to-deploy antenna solution for modern wireless communication systems.

[0009] This invention discloses a high-gain dual-polarized parabolic antenna system. The basic structure of this system includes a parabolic reflector and a feed source. The feed source is cleverly positioned at or near the focal point of the parabolic reflector to ensure that electromagnetic waves radiated from the feed source can be efficiently collected by the reflector and form a highly directional beam. The core innovation of this invention lies in the specific configuration of the feed source. A key component of the feed source is a printed circuit board (PCB). This selective use of the PCB as the substrate for the feed source provides a foundation for subsequent manufacturing processes and integration. Metal oscillator elements are precisely formed on the PCB using an etching process. Etching is a mature and cost-effective manufacturing method that can accurately form complex metal patterns on the PCB surface; these patterns constitute the radiating elements of the antenna. The design of the metal oscillator elements is central to achieving the multifunctionality of this invention. It comprises at least two sets of orthogonally arranged oscillators. This orthogonal arrangement is crucial for achieving dual-polarized radiation, such as vertical and horizontal polarization, or ±45-degree polarization. By independently feeding these two sets of orthogonal elements, the antenna can simultaneously receive or transmit two mutually orthogonal polarized signals, thereby supporting MIMO (Multiple-Input Multiple-Output) technology applications and improving channel capacity and spectral efficiency. A further innovation lies in the design of each of the aforementioned metal element units. Each element (regardless of which polarization it belongs to) integrates a low-frequency radiator for the first frequency band (900MHz band) and a high-frequency radiator for the second frequency band (1800MHz band). This means that the traditional design requiring dual-frequency operation in different antennas or complex multi-layer structures is cleverly integrated into a single element structure in this invention. The low-frequency radiator typically has a relatively large physical size to resonate in the lower 900MHz band; while the high-frequency radiator is relatively small to resonate in the higher 1800MHz band. By precisely designing and optimizing the specific geometry, dimensions, relative positions (e.g., nesting or integration) of these radiating elements, as well as the opening angle of the vibrator arms, a single vibrator can achieve good impedance matching in two widely separated frequency bands, ensuring the efficiency and stability of signal transmission. Ultimately, the feed emits dual-polarized electromagnetic waves through the metal vibrator elements of this scheme. These electromagnetic waves are then reflected by a parabolic reflector, and through the reflector's beam-gathering effect, the scattered electromagnetic waves are focused into a directional beam with high gain and strong directionality, thereby meeting the needs of long-distance communication or high-density user coverage.

[0010] According to a high-gain dual-polarized parabolic antenna system of the present invention, the metal dipole unit includes a first polarized dipole group, which is composed of a first metal dipole arm and a second metal dipole arm symmetrically arranged therewith. The first and second metal dipole arms together form radiation in a specific polarization direction. Specifically, this scheme further defines the specific configuration of the metal dipole unit. In one polarization direction, the dipole unit is specifically designed to consist of two symmetrical metal dipole arms (B1 and B3). These two arms are formed on a PCB by an etching process and are arranged in a symmetrical manner so that they resonate together under feed excitation and generate electromagnetic wave radiation in a specific linear polarization direction. This symmetrical dipole structure is the basic unit for realizing radiation in a specific polarization direction. It can be understood that by etching the first polarized dipole group composed of the first metal dipole arm (B1) and the second metal dipole arm (B3) on the PCB, the present invention provides a basic unit for realizing radiation in a specific polarization direction. This symmetrical arm-like structure ensures that the polarization direction of the radiated electromagnetic wave is clear and that the radiation field pattern has good symmetry. This configuration provides the structural basis for the subsequent realization of dual polarization functionality. By precisely controlling the geometry and relative position of the arms, the desired polarization mode can be effectively excited, thereby ensuring that energy is concentrated in the desired radiation direction and providing a prerequisite for further gain enhancement.

[0011] According to a high-gain dual-polarized parabolic antenna system of the present invention, the metal vibrator unit further includes a second polarized vibrator group. The second polarized vibrator group consists of a third metal vibrator arm and a fourth metal vibrator arm symmetrically arranged therewith. The second polarized vibrator group is arranged on the PCB plane with a 90-degree rotation relative to the first polarized vibrator group, forming a polarization direction orthogonal to the first polarized vibrator group. Specifically, this scheme introduces a second polarized vibrator group (B2 and B4) based on the aforementioned scheme. These also have a symmetrical structure, and crucially, this second polarized vibrator group is arranged on the PCB plane with a 90-degree rotation relative to the first polarized vibrator group (B1 and B3). This orthogonal arrangement is a structural guarantee for achieving dual polarization, enabling the two groups of vibrators to independently radiate two mutually orthogonal electromagnetic wave polarization directions. It can be understood that, based on the first polarized vibrator group (B1, B3), by integrating and orthogonally (90-degree rotation) arranging the second polarized vibrator group (B2, B4), the present invention successfully achieves dual polarization. This orthogonal structure allows the two sets of oscillators to be independently excited and radiate mutually perpendicular electromagnetic wave polarizations, thus enabling multiple independent signals to be transmitted in the same frequency band using different polarizations, or to be used for polarization diversity reception. This dual-polarization capability directly supports the application of advanced wireless communication technologies such as Multiple-Input Multiple-Output (MIMO), significantly improving channel capacity and spectrum utilization, thereby enhancing the throughput and reliability of the communication system.

[0012] According to a high-gain dual-polarized parabolic antenna system of the present invention, each of the first, second, third, and fourth metal dipole arms includes a low-frequency radiating section and a high-frequency radiating section. The high-frequency radiating section is nested or integrated within or near the structure of the low-frequency radiating section. The low-frequency radiating section has a relatively long and wide arm-like structure, while the high-frequency radiating section has a relatively short and narrow arm-like structure. Specifically, this scheme further elaborates on the details of each dipole arm, namely, each arm is not a single structure, but integrates two radiating sections of different sizes: a low-frequency radiating section for the 900MHz frequency band and a high-frequency radiating section for the 1800MHz frequency band. By nesting or integrating the high-frequency radiating section within or near the structure of the low-frequency radiating section, and giving them relatively long / wide and relatively short / narrow geometric characteristics respectively, it is possible to simultaneously support resonance and radiation of two far-separated frequency bands on a single dipole arm. It is understood that by integrating low-frequency and high-frequency radiating sections on each metal vibrator arm, and employing a compact design where the high-frequency radiating section is nested or integrated within or near the low-frequency radiating section, this invention achieves simultaneous support for both 900MHz and 1800MHz operating frequency bands on a single PCB feed. The longer and wider structure of the low-frequency radiating section enables effective resonance and radiation in the 900MHz band, while the shorter and narrower structure of the high-frequency radiating section enables effective resonance and radiation in the 1800MHz band. This design allows the antenna to be compatible with multiple mobile communication network standards such as 2G / 3G / 4G, thereby expanding the antenna's applicability and market compatibility. Simultaneously, this dual-band integrated structure significantly reduces the size and complexity of the feed, simplifies the manufacturing process, and helps reduce production costs and improve product consistency.

[0013] According to a high-gain dual-polarized parabolic antenna system of the present invention, the feed source further includes a director plate formed on the PCB by an etching process. The director plate is located in front of the main radiation direction of the high-frequency radiating section, used to expand the operating bandwidth of the 1800MHz band and increase the gain value of this band. Specifically, this scheme introduces an additional auxiliary structure—director plates (D). These director plates (D) are also formed by PCB etching and strategically placed in front of the main radiation direction of the high-frequency radiating section. As a parasitic oscillator, the director plate (D) is electromagnetically coupled to the high-frequency radiating section, and the radiation characteristics of the 1800MHz band can be adjusted through optimization of its size and position. It can be understood that introducing and optimizing the design of the director plates (D) etched on the PCB in the feed source and placing them in front of the main radiation direction of the high-frequency radiating section can significantly improve the performance of the antenna in the 1800MHz band. As an electromagnetic coupling element, the director plate (D) can effectively guide and shape the radiation field of the high-frequency radiating section, making the radiated energy more concentrated in front. The results of this are twofold: first, it expands the operating bandwidth of the 1800MHz band, improving the antenna's tolerance to frequency variations within that band; second, it increases the gain of the band, further enhancing the antenna's radiation efficiency and long-distance transmission capabilities. This optimization for a specific frequency band ensures the antenna's performance advantages in high-frequency applications, which is particularly significant for high-speed communication systems such as 4G that require high gain and wide bandwidth.

[0014] According to the present invention, a high-gain dual-polarized parabolic antenna system achieves a voltage standing wave ratio (VSWR) of less than or equal to 1.7 within the 900MHz to 1800MHz frequency band. Specifically, this scheme defines the key performance indicator of the antenna system—the VSWR—within the entire dual-band (900MHz to 1800MHz) range and specifies that its value must be less than or equal to 1.7. This is a quantitative requirement for antenna impedance matching performance, comprehensively reflecting the results of all previous structural and parameter optimizations. It can be understood that the antenna system of the present invention achieves a VSWR of less than or equal to 1.7 within a wide frequency band of 900MHz to 1800MHz. This excellent VSWR directly indicates a high degree of impedance matching between the antenna and the feed line throughout the entire operating frequency band. Good impedance matching ensures minimal reflection loss during the transmission of RF signal energy from the transmission line to the antenna, thereby maximizing the radiated power or maximizing the received electromagnetic wave energy. A low VSWR value implies high power transmission efficiency, low insertion loss, and stable signal transmission. This is crucial for wireless communication systems that require broadband compatibility and high efficiency, ensuring stable connection and efficient transmission of signals under different frequency bands and communication standards, reducing power consumption at the transmitter and damage to equipment, and improving the reliability of the entire system.

[0015] Based on the above, this invention also discloses a method for maintaining the performance of a high-gain dual-polarized parabolic antenna system, comprising the following steps: Sensor deployment step: integrating a current monitoring sensor, a port characteristic monitoring sensor, and an environmental parameter sensor on the feed unit; Data acquisition configuration step: configuring the data acquisition unit, establishing connection relationships with each sensor, and setting the data acquisition period and parameters; Data acquisition and processing step: acquiring the output signals of each sensor at a set period through the data acquisition unit, and filtering and digitizing the acquired signals; Data output step: transmitting the processed data to an external processing unit or storing it in a local storage medium through a communication interface; wherein, the sensor deployment step provides the signal source basis for the data acquisition configuration step, the parameter setting in the data acquisition configuration step controls the execution timing of the data acquisition and processing step, and the output results of the data acquisition and processing step are externally transmitted through the data output step. Specifically, this method first integrates three types of key sensors on the feed unit: a current monitoring sensor for real-time sensing of the RF current state of each metal vibrator arm, a port characteristic monitoring sensor for monitoring the reflection coefficient and mutual coupling characteristics of the polarization port, and an environmental parameter sensor for acquiring external condition information such as temperature and humidity. Subsequently, a data acquisition unit is configured to establish the connection topology of the sensor network and a timing control mechanism for data acquisition. The data acquisition and processing stage automatically collects signals from each sensor according to a preset cycle, and performs filtering and digital preprocessing to ensure data quality. Finally, the processed data is transmitted to an external processing unit or local storage via a standardized communication interface, providing a data foundation for subsequent intelligent analysis. Its technical advantages are as follows: From a systems engineering perspective, the establishment of this infrastructure first achieves full-coverage sensing capability for key feedhorn parameters. By integrating miniature sensors on the PCB, the installation complexity and reliability issues of traditional external monitoring equipment are avoided, while ensuring monitoring accuracy and real-time performance. The unified configuration and periodic acquisition mechanism of the data acquisition unit ensure time synchronization and format standardization of multi-source heterogeneous data, laying a high-quality data foundation for subsequent feature extraction and pattern recognition. The filtering and digital processing stages effectively suppress noise interference in the radio frequency environment, improving the signal-to-noise ratio of the sensor data. The standardized data output interface ensures the system's scalability and compatibility with upper-layer processing systems. In summary, this method establishes a high-precision, high-reliability, and scalable feedhorn status sensing platform, providing a solid technical foundation for intelligent antenna health management.

[0016] According to a method for maintaining the performance of a high-gain dual-polarized parabolic antenna system based on the present invention, the method further includes: extracting feed health status characteristic parameters from the output data of the data acquisition and processing, wherein the characteristic parameters include: calculating the current amplitude deviation of each metal vibrator arm, obtained by the absolute value of the difference between the current monitored current amplitude and the reference current amplitude; calculating the current phase deviation of each metal vibrator arm, obtained by the absolute value of the difference between the current monitored current phase and the reference current phase; extracting the percentage change in the mutual coupling coefficient amplitude and the phase drift of the mutual coupling coefficient between polarization ports; calculating the mutual coupling fingerprint deviation metric based on the percentage change in the mutual coupling coefficient amplitude and the phase drift; and combining the current amplitude deviation, current phase deviation, mutual coupling coefficient change parameters, mutual coupling fingerprint deviation metric, and environmental parameters to construct a comprehensive feature vector. In summary, this scheme, based on the aforementioned data acquisition, achieves intelligent conversion from raw sensor data to health status characteristics. This scheme constructs a multi-dimensional health feature extraction algorithm targeting the electromagnetic characteristics of dual-polarized feeds. Specifically, by calculating the deviation of the current parameters (amplitude and phase) of each metal oscillator arm relative to a healthy baseline state, the performance changes of individual oscillators are quantified. Simultaneously, the percentage change in amplitude and phase drift of the mutual coupling coefficient between polarization ports are extracted, establishing the concept of "mutual coupling fingerprint," and the corresponding deviation metric is calculated. This scheme organically integrates individual oscillator characteristics, mutual coupling characteristics, and environmental parameters to construct a comprehensive feature vector capable of fully characterizing the feed health state. Its technical advantages are: from a signal processing theory perspective, this feature extraction scheme achieves an effective mapping from high-dimensional sensor data to a low-dimensional feature space. The calculation of current amplitude and phase deviation directly reflects the changes in the resonant characteristics of each oscillator arm, sensitively capturing performance degradation caused by physical damage, connection deterioration, or material aging. The introduction of the mutual coupling fingerprint feature is an innovation of this scheme, utilizing the stability and uniqueness of the coupling relationship between polarization ports in a dual-polarized antenna; by monitoring changes in coupling characteristics, anomalies in the internal electromagnetic environment can be effectively identified. The comprehensive calculation of the deviation metric, through weighted fusion of amplitude and phase information, improves the sensitivity and accuracy of fault detection. The construction of comprehensive feature vectors enables the fusion of multi-source information, enhancing the completeness and robustness of health status representation. This approach significantly improves the ability to extract effective health information from raw data, providing high-quality feature input for subsequent intelligent diagnosis, while simultaneously reducing data dimensionality and improving processing efficiency.

[0017] According to the present invention, a method for maintaining the performance of a high-gain dual-polarized parabolic antenna system further includes: constructing a health diagnostic model using a machine learning algorithm; training the diagnostic model using electromagnetic simulation data and laboratory accelerated aging test data to establish a mapping relationship from the comprehensive feature vector to health scores, fault types, and fault locations; deploying the trained diagnostic model to a data acquisition unit or an edge computing unit; inputting the real-time obtained comprehensive feature vector into the diagnostic model, and outputting the health scores of each metal vibrator arm, the overall health score of the feed, fault mode identification results, and fault location information. In summary, this scheme constructs an artificial intelligence-based health diagnostic system based on the aforementioned comprehensive feature vector. This scheme employs various mature machine learning algorithms, including support vector machines, random forests, gradient boosting trees, or neural networks, to adapt to diagnostic tasks of varying complexity. The training data comes from electromagnetic simulation and laboratory accelerated aging tests, ensuring the model's learning coverage of various fault modes. By establishing a nonlinear mapping relationship from feature vectors to health scores, fault types, and fault locations, intelligent conversion from data to diagnostic conclusions is achieved. The model deployment employs an edge computing architecture, enabling real-time inference locally and outputting multi-level diagnostic information including individual oscillator health scores, overall health scores, fault mode recognition, and precise location. Its technical advantages are as follows: From a machine learning theory perspective, this intelligent diagnostic system represents a technological leap from traditional rule-based fault detection to data-driven pattern recognition. A multi-algorithm selection strategy ensures adaptability to different fault characteristic patterns; support vector machines are suitable for small-sample, high-dimensional problems; random forests have good generalization capabilities; gradient boosting trees excel in handling nonlinear relationships; and neural networks possess powerful complex pattern learning capabilities. The combined training with simulation and experimental data ensures the model's theoretical completeness and practical applicability. The edge computing deployment strategy achieves low-latency real-time diagnosis, avoiding data transmission delays and security risks. The multi-level output structure provides comprehensive diagnostic information, from individual to overall, from qualitative to quantitative, and from detection to location. This solution significantly improves the accuracy, real-time performance, and intelligence of fault diagnosis, realizing a shift from passive maintenance to proactive prediction, and providing reliable technical support for precise and predictive maintenance.

[0018] According to a performance maintenance method for a high-gain dual-polarized parabolic antenna system based on the present invention, the method further includes: initiating intelligent polarization reconfiguration when the overall health score of the feed is lower than a preset threshold; identifying harmful coupling paths that cause a decrease in polarization isolation based on the fault mode identification results and fault location information; estimating the complex coefficients of cross-polarization leakage and calculating compensation parameters for suppressing the harmful coupling paths; performing cross-compensation processing on the original polarization port signals by adjusting the amplitude weights and phase weights of the transmitted signals at the two polarization ports; running an optimization algorithm to search for the optimal combination of complex weights to maximize the comprehensive utility function including the signal-to-interference-plus-noise ratio, cross-polarization leakage power, and health deviation; and applying the calculated optimized weight parameters to the base station digital signal processing link to dynamically adjust the baseband signal fed to the antenna polarization ports. In summary, this scheme achieves an adaptive performance recovery mechanism for the antenna system based on the aforementioned intelligent diagnostic results. When the diagnostic system detects that the health score is lower than a preset threshold, the scheme initiates the intelligent polarization reconfiguration process. First, based on the fault mode and location information, harmful coupling paths that cause a decrease in polarization isolation are identified, and the complex characteristic parameters of cross-polarization leakage are estimated. Subsequently, targeted compensation parameters are calculated, and the amplitude and phase of the transmitted signals at the two polarization ports are precisely adjusted using digital domain signal preprocessing techniques. This scheme employs a multi-objective optimization algorithm, comprehensively considering factors such as signal quality, cross-polarization suppression, and health deviation, to search for the optimal combination of complex weights. Finally, the optimization results are applied to the digital signal processing link of the base station to achieve dynamic adjustment of the baseband signal fed to the antenna. Its technical advantages are: from the perspective of adaptive signal processing theory, this polarization reconstruction scheme achieves proactive performance compensation even when physical defects cannot be repaired. The identification of harmful coupling paths is based on the reciprocity principle in electromagnetic field theory; by analyzing the impact of faults on the field distribution, the root cause of performance degradation is accurately located. The estimation of the complex coefficients of cross-polarization leakage establishes a channel model under fault conditions, providing a theoretical basis for the compensation algorithm. The digital domain signal preprocessing technique borrows the precoding concept from MIMO systems, actively introducing reverse compensation at the transmitter to offset harmful effects at the receiver. The introduction of the multi-objective optimization algorithm ensures a balance between different indicators during performance recovery, avoiding system performance imbalances that may result from optimizing a single indicator. Real-time adjustment of the base station digital signal processing link enables software-defined antenna characteristics, greatly enhancing the system's flexibility and adaptability. This solution significantly improves the antenna system's service continuity and performance maintenance capabilities under fault conditions, realizing an innovative solution path from hardware failure to software compensation, and providing important technical support for the high-reliability operation of communication systems.

[0019] This invention discloses a high-gain dual-polarized parabolic antenna system. It integrates a dual-band (900MHz and 1800MHz) dual-polarized metal vibrator unit on a single printed circuit board (PCB) using an etching process. This PCB-integrated design significantly reduces the number of components and assembly steps compared to traditional feedhorns that employ multi-layer boards, multi-component splicing, or complex three-dimensional structures. This simplifies the feedhorn manufacturing and assembly process, effectively reducing production costs while improving product manufacturing consistency and reliability. Furthermore, since each vibrator in the metal vibrator unit integrates a low-frequency radiator for the first frequency band and a high-frequency radiator for the second frequency band, the antenna achieves good impedance matching in both the 900MHz and 1800MHz target frequency bands. This design, integrating dual-frequency resonant characteristics into a single vibrator, avoids the complex coupling problems between radiating elements of different frequency bands. This allows the antenna to maintain excellent voltage standing wave ratio (VSWR) within a wide frequency band of 900MHz-1800MHz, especially across two relatively far frequency bands (900MHz and 1800MHz), achieving a VSWR ≤ 1.7. This ensures high efficiency and stability of RF signal transmission and reduces power loss. Furthermore, the metal oscillator unit comprises at least two sets of orthogonally arranged oscillators, forming radiation in two orthogonal polarization directions. This orthogonal arrangement is a direct and effective way to achieve dual polarization, resulting in high isolation between the two polarization channels. This enables the antenna to better support MIMO (Multiple-Input Multiple-Output) technology in modern wireless communication systems, effectively improving the system's channel capacity, spectrum utilization, and communication reliability, meeting the demands of high data rate transmission. Moreover, the parabolic reflector used in this invention inherently uses a focusing effect to converge the electromagnetic waves radiated from the feed source into a high-gain directional beam. Meanwhile, the feed's dual-band (900MHz and 1800MHz) capability allows it to support both bands simultaneously, thus providing excellent coverage and anti-interference capabilities. This makes it particularly suitable for scenarios requiring rapid deployment and high-density user access, such as emergency communications and temporary base stations for large events. Furthermore, its compatibility with both 900MHz and 1800MHz bands enables the antenna to adapt to and support the coexistence of multiple mobile communication networks, including 2G, 3G, and 4G, enhancing the system's flexibility and practicality. In summary, this invention, through its innovative design integrating a dual-band, dual-polarized metal vibrator unit on a PCB, achieves a compact structure and low-cost manufacturing while significantly improving the antenna's electrical performance over a wide bandwidth, providing an efficient and flexible solution for modern wireless communication. Attached Figure Description

[0020] To more clearly illustrate the technical solutions in this invention or the prior art, the accompanying drawings used in the description of the embodiments or the prior art will be briefly introduced below.

[0021] Figure 1 This is a schematic diagram of the antenna feed structure of the present invention;

[0022] Figure 2 This is a schematic diagram of the metal oscillator unit layout of the present invention. Detailed Implementation

[0023] The high-gain dual-polarized parabolic antenna system of the present invention will now be described in detail with reference to this application. The embodiments disclosed in this specification are for illustrative purposes only and are not intended to limit the scope of protection of the present invention.

[0024] This invention provides a high-gain dual-polarized parabolic antenna system, with reference to... Figure 1 The high-gain dual-polarized parabolic antenna system of this embodiment mainly includes a parabolic reflector and a feed. The feed is located at the focal or near-focal region of the parabolic reflector. This location ensures that the spherical or quasi-spherical waves radiated by the feed are effectively reflected by the parabolic reflector to form a highly directional planar beam, thereby achieving the high-gain characteristics of the antenna system. The parabolic reflector adopts a parabolic antenna reflector structure known in the art.

[0025] The antenna system also includes an antenna base to support the entire system and provide a stable mounting foundation. The feedhorn is connected to the parabolic reflector via a feedhorn flange, which is made of precision-machined metal to ensure accurate positioning and a secure connection between the feedhorn and the reflector. The feedhorn flange and the antenna base are connected by an aluminum tube, which not only provides mechanical support but also houses the feed cable for efficient signal transmission.

[0026] To protect the electronic components of the feed from environmental factors, an antenna housing is installed on the outside of the feed. The antenna housing is made of a low-dielectric-constant engineering plastic material, possessing excellent weather resistance and electromagnetic transparency. Its dielectric constant is typically controlled between 2.0 and 3.0, and its loss tangent is less than 0.01, ensuring minimal impact on antenna performance. The antenna housing design also considers waterproof sealing requirements, achieving a protection rating of IP65 or higher.

[0027] The core component of the feed is a printed circuit board (PCB), manufactured using standard PCB processes, ensuring good dimensional accuracy and manufacturing consistency. Metal oscillator units B are formed on the PCB through an etching process, constituting the main radiating structure of the feed. The advantages of using PCB etching technology are significantly reduced manufacturing costs, improved production efficiency, and ensured accuracy and repeatability of the oscillator structure.

[0028] Reference Figure 2The metal oscillator unit B includes at least two sets of orthogonally arranged oscillators, specifically a first polarized oscillator group and a second polarized oscillator group. The first polarized oscillator group consists of a first metal oscillator arm B1 and a second metal oscillator arm B3 symmetrically arranged therewith. The first metal oscillator arm B1 and the second metal oscillator arm B3 together form radiation in a polarization direction. The second polarized oscillator group consists of a third metal oscillator arm B2 and a fourth metal oscillator arm B4 symmetrically arranged therewith. The second polarized oscillator group is arranged on the PCB plane rotated 90 degrees relative to the first polarized oscillator group, forming radiation in a polarization direction orthogonal to the first polarized oscillator group.

[0029] like Figure 2 As shown, the four metal oscillator arms B1, B2, B3, and B4 exhibit a symmetrical petal-shaped or butterfly-wing-shaped geometry on the PCB. This unique geometric design is not only aesthetically pleasing but, more importantly, optimizes current distribution and radiation characteristics. The edge contours of each oscillator arm are carefully designed with smooth, curved transitions to avoid current concentration and unnecessary high-frequency harmonics that may result from sharp corners. A circular power supply area is located in the center of the PCB, integrating the power supply network and impedance matching circuitry.

[0030] This orthogonal arrangement design achieves high-quality dual polarization, supports MIMO technology applications, and effectively enhances channel capacity and communication reliability. The symmetry of the four arms ensures the antenna's omnidirectional radiation characteristics in the horizontal plane while maintaining good polarization purity.

[0031] Each of the first metal oscillator arm B1, the second metal oscillator arm B3, the third metal oscillator arm B2, and the fourth metal oscillator arm B4 includes a low-frequency radiating section and a high-frequency radiating section. Specifically, the first metal oscillator arm B1 includes a low-frequency radiating section mainly used for radiation in the 900MHz frequency band and a high-frequency radiating section mainly used for radiation in the 1800MHz frequency band; the second metal oscillator arm B3 includes both a low-frequency radiating section and a high-frequency radiating section; the third metal oscillator arm B2 includes both a low-frequency radiating section and a high-frequency radiating section; and the fourth metal oscillator arm B4 includes both a low-frequency radiating section and a high-frequency radiating section.

[0032] The low-frequency radiating section has a relatively long and wide arm-like structure, with a length approximately one-quarter of the operating wavelength in the 900MHz band, suitable for achieving good radiation efficiency in the 900MHz band. The high-frequency radiating section has a relatively short and narrow arm-like structure, with a length approximately one-quarter of the operating wavelength in the 1800MHz band, to meet the radiation requirements of the 1800MHz band. The high-frequency radiating section is nested or integrated within or near the structure of the low-frequency radiating section. This integrated design allows a single oscillator arm to achieve effective radiation in two different frequency bands, significantly improving spectral efficiency.

[0033] By precisely adjusting the length, width, shape, spacing, and overall opening angle of the low-frequency and high-frequency radiating sections, the input impedance of the antenna in both the 900MHz and 1800MHz frequency bands can be optimized to approach the characteristic impedance of the feed line (50 ohms), thus achieving good impedance matching. The opening angle of the vibrator arm has been optimized to ensure optimal impedance matching in both frequency bands.

[0034] Furthermore, the feed also includes a director piece D. The director piece D is formed on the PCB using an etching process, employing the same manufacturing process as the metal oscillator unit B, ensuring integrated structural design. Figure 2 As shown, the director element D has a circular structure and is located above or in front of the central region of the metal oscillator unit B, forming a cooperative working relationship with the high-frequency radiating part. The circular design of the director element D has the advantage of symmetry, which can provide a uniform electromagnetic coupling enhancement effect to the high-frequency radiating part in four directions. The size of the director element D and its distance from the center of the metal oscillator unit B are optimized to achieve effective improvement in the performance of the 1800MHz band. The technical effect of this circular director element design is reflected in the fact that the director element D can effectively expand the operating bandwidth of the 1800MHz band and improve the forward gain of this band. At the same time, the circular structure ensures uniform improvement of radiation characteristics in all directions and avoids directional deviation. The working principle of the director element D is based on the secondary radiation effect of electromagnetic waves. When the high-frequency radiating part radiates electromagnetic waves in the 1800MHz band, the director element D, as a passive radiating unit, will generate an induced current and form secondary radiation. By precisely controlling the size and position of the guide plate D, the secondary radiation and the main radiation are superimposed in phase in the forward direction and canceled out in phase in the backward direction, thereby achieving pattern shaping and gain enhancement.

[0035] The power supply structure and working principle of this embodiment are as follows:

[0036] The antenna system is fed using a differential feeding method. For the first polarized dipole group, the inner conductor of the external feed cable is connected to the feed point of the first metal dipole arm B1, and the outer conductor is connected to the feed point of the second metal dipole arm B3. The feed point is located at the root of the dipole arm, i.e., near the center of the PCB. The first metal dipole arm B1 and the second metal dipole arm B3 constitute a half-wavelength symmetrical dipole excited by the feed cable, radiating electromagnetic waves simultaneously in the 900MHz and 1800MHz frequency bands.

[0037] The second polarization oscillator group is fed in a similar manner to the first polarization oscillator group, using an independent feed cable for excitation. This independent feed design for the two oscillators ensures good isolation between the dual-polarization signals, meeting the polarization isolation requirements of MIMO systems.

[0038] The low-frequency and high-frequency radiating sections integrated on each arm of the metal oscillator unit B work collaboratively via electromagnetic coupling. In the 900MHz band, the low-frequency radiating section dominates, while the high-frequency radiating section, due to its relatively small size, has a smaller impact on radiation in this band. In the 1800MHz band, the high-frequency radiating section dominates, while the low-frequency radiating section, although larger in size, has its impact on the 1800MHz band effectively controlled through precise geometric design, preventing significant performance degradation.

[0039] Through the above structural design, especially the specific geometry, size, and relative layout of the metal vibrator unit B on the PCB, and the synergistic effect of the guide plate D, the antenna system of this invention achieves the following technical effects: 1. Good impedance matching with a voltage standing wave ratio (VSWR) of less than or equal to 1.7 within a wide frequency band of 900MHz to 1800MHz, ensuring the stability and efficiency of signal transmission. 2. Excellent dual-polarization performance, with small gain difference between the two orthogonal polarization directions and high polarization isolation, meeting the requirements of modern communication systems for dual-polarized antennas. 3. High gain characteristics: High gain can be achieved in both the 900MHz and 1800MHz frequency bands, meeting the application requirements of high-gain antennas. The diameter and focal diameter ratio of the parabolic reflector are designed according to application requirements to optimize the matching of gain and beamwidth. 4. Good directivity: Narrow beamwidth in both operating frequency bands, with effective control of sidelobe levels, reducing interference to adjacent base stations.

[0040] Based on the antenna system described in this embodiment, this embodiment also provides a method for maintaining the performance of a high-gain dual-polarized parabolic antenna system. This method ensures that the antenna can maintain the availability and quality of the communication link to the maximum extent even when the performance of the feed element may deteriorate or fail, through real-time monitoring, intelligent diagnosis, and adaptive reconfiguration. The specific implementation details are as follows:

[0041] I. Perform the sensor deployment steps, as follows:

[0042] On the printed circuit board (PCB) of the feed unit, sensors are integrated and deployed for each metal arm constituting the dual-polarized antenna. Specifically, for the first polarized oscillator group consisting of the first metal arm B1 and the second metal arm B3, and the second polarized oscillator group consisting of the third metal arm B2 and the fourth metal arm B4, miniature sensors are integrated along their current paths using PCB etching. Specifically, on the PCB of the feed unit, for each of the dual-polarized metal arms B1, B2, B3, and B4, miniature current sensing structures (optionally Rogowski coils and optional miniature strain gauges) are integrated to achieve precise monitoring of the RF current amplitude, phase, and minute structural deformation of each oscillator arm. The current monitoring sensors are deployed using miniature Rogowski coils or equivalent current sensing structures, and the sensors monitor the RF current flowing through each oscillator arm in a non-contact manner. The Rogowski coil works on the principle of electromagnetic induction. When radio frequency current flows through the oscillator arm, an induced electromotive force is generated in the coil. The amplitude of the induced electromotive force is proportional to the amplitude of the measured current, and the phase is kept in a fixed relationship with the phase of the measured current, thereby realizing accurate monitoring of radio frequency current.

[0043] Port characteristic monitoring sensors are deployed at the two physically polarized ports of the feed. The V-polarized port is formed by the convergence of feed points B1 and B3, while the H-polarized port is formed by the convergence of feed points B2 and B4. The reflection coefficient of each port is monitored either through the RF detection port at each port or through an external miniature directional coupler. and And the isolation or coupling coefficient between ports. and The directional coupler employs a microstrip line structure with a coupling range of -20dB to -30dB to minimize the impact on the main signal path while providing sufficient monitoring signal strength. These parameters directly reflect the voltage standing wave ratio (VSWR) and polarization coupling of the antenna.

[0044] In addition, specific structures are etched near key stress points of the oscillator arm to serve as micro-strain gauges, sensing minute deformations caused by physical damage such as microcracks and other deformations. Environmental parameter sensors, including temperature and humidity sensors, are integrated onto the PCB or inside the feed cavity, respectively, to monitor the feed's operating environment parameters. The temperature sensor uses a platinum resistance thermometer (RTD) or a thermistor (NTC), with a measurement range of -40℃ to +85℃ and an accuracy of ±0.5℃. The humidity sensor uses a capacitive humidity sensor, with a measurement range of 0% to 100% relative humidity and an accuracy of ±2%RH.

[0045] This step aims to achieve more comprehensive data acquisition, specifically through multi-dimensional and refined real-time sensing of key electrical parameters such as current and S-parameters, and physical parameters such as deformation, temperature, and humidity within the feed unit. High-precision sensing technology captures early, subtle performance changes in the feed unit caused by aging, environmental influences, or minor damage, providing a raw data foundation for subsequent health diagnosis and fault early warning. Furthermore, the physical state and electromagnetic performance of the feed are converted into quantifiable and analyzable digital signals, laying the groundwork for the introduction of AI-based intelligent algorithms. Independent monitoring of each oscillator arm makes it possible to pinpoint specific components to identify subsequent faults.

[0046] II. Perform the data collection configuration steps, as follows:

[0047] The data acquisition unit (DCU) is implemented using an onboard microcontroller unit (MCU) or by connecting a compact data acquisition module. The MCU is a 32-bit processor based on the existing ARM Cortex-M4 architecture, featuring a floating-point unit (FPU) and a digital signal processor (DSP), operating at a frequency of 168MHz, and containing 512KB of flash memory and 192KB of RAM.

[0048] The detailed operation of the data acquisition unit configuration involves integrating an existing onboard microcontroller unit (MCU) onto the feed source or connecting a compact data acquisition module as a DCU. The DCU is responsible for periodically acquiring sensor data, with a configurable acquisition period, for example, every 1 second to several minutes. The connection relationships between the data acquisition unit and each sensor are established as follows: The current monitoring sensor is connected via a high-precision analog-to-digital converter (ADC). The ADC uses 16-bit resolution, a sampling rate of 1 MSPS, and features differential input and a programmable gain amplifier (PGA). The port characteristic monitoring sensor is connected to the ADC via an RF switch and a downconverter to monitor the amplitude and phase of the reflection coefficient and mutual coupling coefficient. The environmental parameter sensor is connected to the MCU via an I2C bus to support digital output and temperature compensation functions.

[0049] The specific data collected periodically by the DCU includes: the current amplitude of each oscillator arm Bk (k=1,2,3,4). and phase The voltage standing wave ratios (VSWR) and VSWR_H of the two polarization ports can be obtained from the reflection coefficients of the corresponding ports. and The modulus value is calculated; the mutual coupling coefficient between polarization ports is obtained. and The amplitude and phase; and the ambient temperature T and humidity H. The voltage standing wave ratio (VSWR) is calculated using the standard formula. The VSWR_V of the V-polarized port is expressed by the relationship VSWR_V = (1 + | |) / (1 - | |) calculate, where | | is the reflection coefficient of the V-polarized port. The modulus value; the calculation of VSWR_H is similar, using... The modulus.

[0050] The data acquisition period parameter is set to a configurable mode, with a default period ranging from every 1 second to several minutes. Specifically, the acquisition period for current monitoring data is set to 1 second to capture rapid changes in RF current; the acquisition period for port characteristic monitoring data is set to 5 seconds to balance monitoring accuracy and system resource consumption; and the acquisition period for environmental parameters is set to 60 seconds because environmental temperature and humidity change relatively slowly.

[0051] The technical benefit of this step lies in establishing a complete data acquisition architecture, ensuring that data from various sensors can be collected according to preset time sequences and accuracy requirements, providing a stable and reliable data source for subsequent feature extraction and AI diagnostics. Through standardized data acquisition configuration, unified management and coordinated acquisition of multi-source heterogeneous sensor data are achieved.

[0052] III. The data acquisition and processing steps are implemented as follows:

[0053] The detailed data acquisition and processing process includes the DCU actively querying all sensors according to a preset cycle to collect raw data, including vibrator arm current data, port S-parameters, and ambient temperature and humidity. The DCU performs preliminary signal conditioning on the collected raw data, including filtering, amplification, and analog-to-digital conversion if necessary. The processed data is temporarily stored in the DCU's local memory or transmitted in real time to higher-level processing units such as edge computing units or base station BBUs via standard communication interfaces such as SPI, I2C, UART, and Ethernet.

[0054] The process of filtering and digitizing the acquired signal includes: First, the original analog signal is subjected to anti-aliasing low-pass filtering using an 8th-order Butterworth filter with a cutoff frequency set to 40% of the ADC sampling frequency; then, analog-to-digital conversion is performed using a 16-bit ADC, achieving a conversion accuracy of 65,536 discrete levels; next, the digitized signal is digitally filtered using a finite impulse response (FIR) filter to remove high-frequency noise and power frequency interference; finally, amplitude and phase extraction and calibration are performed, extracting the amplitude and phase information of the signal using digital signal processing algorithms and correcting the amplitude and phase based on pre-stored calibration data.

[0055] The technical advantage of this step lies in achieving high-precision, low-noise data acquisition. Through multi-level filtering and calibration, the accuracy and reliability of the monitoring data are ensured, laying a data quality foundation for subsequent feature extraction and AI diagnostics. A standardized data processing workflow transforms the physical state and electromagnetic properties of the feed source into quantifiable and analyzable digital signals.

[0056] IV. Perform the data output steps, as follows:

[0057] The processed data is transmitted externally via standard communication interfaces. These interfaces include SPI, I2C, UART, and Ethernet. The SPI interface is used for high-speed data transmission, with a transmission rate of up to 10 Mbps; the I2C interface is used for low-speed control signal transmission; the UART interface provides asynchronous serial communication; and the Ethernet interface supports the TCP / IP protocol stack, enabling connection to upper-layer networks.

[0058] Data storage employs a dual-mode design: local storage and network transmission. Local storage uses 32MB of non-volatile flash memory and employs a circular buffer management system, automatically overwriting the oldest data when the storage space is full. Network transmission uses a real-time transmission mode, where processed data is transmitted in real-time to the edge computing unit or base station BBU via an Ethernet interface.

[0059] The data format adopts the standardized JSON format, which includes information such as timestamp, sensor ID, data type, value, and unit. The data packet structure is designed as follows: {"timestamp": "YYYY-MM-DD HH:MM:SS", "sensor_id": "Bk_current", "data_type": "amplitude", "value": xx.xx, "unit": "mA"}.

[0060] The technical benefit of this step lies in achieving standardized data transmission and storage, ensuring data integrity and traceability, and providing a foundation for subsequent distributed processing and long-term trend analysis. Through support for multiple communication interfaces, compatibility and interoperability with different types of external systems are achieved.

[0061] V. Perform the steps for extracting health status feature parameters, as follows:

[0062] The detailed feature extraction process involves a higher-level processing unit or a DCU with sufficient computing power receiving the raw sensing data from step one. For each individual oscillator arm, the deviation between its current current amplitude and phase and the health baseline is calculated. For the polarization port characteristics, the change in the current VSWR and the key "mutual coupling fingerprint" feature are calculated. A comprehensive "mutual coupling fingerprint deviation metric (MFDD)" is calculated according to a specific formula to quantify the degree of deviation in the overall coupling state. The individual oscillator arm features, mutual coupling fingerprint features, and environmental parameters are integrated into a multi-dimensional comprehensive feature vector F.

[0063] Feature parameters that can effectively characterize the health status of the feed source are extracted from the output data of data acquisition and processing. The extraction of individual oscillator arm health characteristics includes current deviation calculation and characteristic frequency point offset analysis.

[0064] The current amplitude deviation of each metal oscillator arm is calculated using the following formula:

[0065] ;

[0066] The detailed meanings of each parameter in this formula are as follows: is the absolute value of the current amplitude deviation of the k-th oscillator arm (Bk), in milliamperes (mA), representing the degree of deviation of the current amplitude from the healthy reference state. The value is the current amplitude of the radio frequency current currently monitored in the k-th oscillator arm, in milliamperes (mA), which is obtained in real time through current monitoring sensors such as Rogowski coils. This represents the RF current amplitude of the k-th oscillator arm under healthy baseline conditions, measured in milliamperes (mA), obtained through factory calibration or statistical averaging during healthy operation. k is the index of the oscillator arm, with values ​​of 1, 2, 3, and 4, corresponding to the first, second, third, and fourth metal oscillator arms, respectively.

[0067] The current phase deviation of each metal oscillator arm is calculated using the formula:

[0068] ;

[0069] The detailed meanings of each parameter in this formula are as follows: The absolute value of the current phase deviation of the k-th oscillator arm, in degrees (°) or radians (rad), characterizes the degree of deviation of the current phase from the healthy reference state. The current phase of the radio frequency current currently monitored for the kth oscillator arm is expressed in degrees (°) or radians (rad) and is obtained in real time through a phase detection circuit. The RF current phase of the k-th oscillator arm under healthy reference conditions is expressed in degrees (°) or radians (rad) and serves as a reference.

[0070] The reference value is derived from the statistical average of antenna factory calibration or healthy operation, and a stable reference is obtained through least squares fitting. The phase deviation calculation takes into account the 2π periodicity and adopts the principle of minimum angle difference for calculation.

[0071] The characteristic frequency shift is monitored by analyzing the response of the oscillator arm current or port S-parameters under a frequency sweep test, which can be performed by injecting a test signal during non-operational time slots. The resonant frequency shift is calculated using the formula:

[0072] ;

[0073] The detailed meanings of each parameter in this formula are as follows: This represents the resonant frequency offset of the k-th oscillator arm, measured in Hertz (Hz) or Megahertz (MHz). A positive value indicates an upward shift in frequency, while a negative value indicates a downward shift. This represents the resonant frequency value of the k-th oscillator arm, currently monitored through frequency sweep testing or other methods, in Hertz (Hz) or Megahertz (MHz). The resonant frequency of the k-th oscillator arm under healthy reference conditions is expressed in Hertz (Hz) or Megahertz (MHz), serving as a reference for frequency offset.

[0074] The percentage change in the amplitude of the mutual coupling coefficient between polarization ports is calculated using the formula:

[0075] ;

[0076] The detailed meanings of each parameter in this formula are as follows: This represents the percentage change in the amplitude of the mutual coupling coefficient from the V-polarized port to the H-polarized port, characterizing the relative change in the coupling strength from V to H. The amplitude of the mutual coupling coefficient between the V-polarized port and the H-polarized port is currently monitored. It is a dimensionless linear value or expressed in decibels (dB). The amplitude of the mutual coupling coefficient between the V-polarized port and the H-polarized port under healthy baseline conditions is used as a reference for calculating the percentage change. The ratio of the signal detected at the H-polarized port to the incident signal at the V-port when a signal is fed from the V-polarized port represents the degree of coupling or leakage from the V-polarized to the H-polarized port.

[0077] The phase drift of the mutual coupling coefficient is calculated using the formula:

[0078] ;

[0079] The detailed meanings of each parameter in this formula are as follows: The phase drift is the mutual coupling coefficient from the V-polarized port to the H-polarized port, expressed in degrees (°) or radians (rad). The phase of the mutual coupling coefficient between the V-polarized port and the H-polarized port currently being monitored is expressed in degrees (°) or radians (rad). The phase of the mutual coupling coefficient between the V-polarized port and the H-polarized port under healthy reference conditions, in degrees (°) or radians (rad).

[0080] Similarly, for the mutual coupling coefficient in the H-to-V direction, there is a corresponding formula:

[0081] ;

[0082] ;

[0083] The mutual coupling fingerprint bias metric MFDD is calculated using a weighted synthesis method:

[0084] ;

[0085] The detailed meanings of each parameter in this formula are as follows:

[0086] The Mutual-coupling Fingerprint Deviation Degree is a measure of mutual-coupling fingerprint deviation. It is a comprehensive quantification of the degree to which the feed-source mutual-coupling state deviates from the baseline. The larger the value, the more severe the deviation. This is a weighting factor for the amplitude change of the mutual coupling coefficient, with a value ranging from 0 to 1, used to adjust the importance of amplitude change in the comprehensive evaluation. This is a weighting factor for the phase change of the mutual coupling coefficient, with a value ranging from 0 to 1. Typically, wamp + wphase = 1, which is used to adjust the importance of phase change in the overall evaluation. This is the absolute value of the percentage change in the mutual coupling coefficient amplitude from the V-polarized port to the H-polarized port. This is the absolute value of the percentage change in the mutual coupling coefficient amplitude from the H-polarized port to the V-polarized port. This is the absolute value of the phase drift of the mutual coupling coefficient from the V-polarized port to the H-polarized port, expressed in degrees (°) or radians (rad). This is the absolute value of the phase drift of the mutual coupling coefficient from the H-polarized port to the V-polarized port, expressed in degrees (°) or radians (rad). This is a phase normalization constant, such as 180 degrees or π radians, used to normalize the phase deviation to a comparable range, such as 0-1.

[0087] The reason and necessity for introducing MFDD is that simple single-parameter changes may not be sufficient to fully reflect complex changes in coupling states. MFDD provides a comprehensive index that, through weighted amplitude and phase changes, can more sensitively capture changes in the internal electromagnetic environment caused by oscillator arm damage, deformation, or connection deterioration. These changes are often first reflected in the coupling characteristics between ports.

[0088] The construction of the comprehensive feature vector combines the aforementioned individual oscillator arm health features, mutual coupling fingerprint features, and environmental parameters into a multi-dimensional vector.

[0089] ;

[0090] The detailed meanings of each parameter in the comprehensive feature vector F are as follows: F is the comprehensive feature vector of the feed source state, which is a multi-dimensional array containing 19 elements that comprehensively describes the health status of the feed source. , , , Let represent the absolute values ​​of the current amplitude deviations of the first to fourth oscillator arms, respectively. Let represent the absolute values ​​of the current phase deviation of the first to fourth oscillator arms, respectively. Let represent the resonant frequency offsets of the first to fourth oscillator arms, respectively. This represents the percentage change in the amplitude of the mutual coupling coefficient from port V to port H. The phase drift of the mutual coupling coefficients from the V to H ports. This represents the percentage change in the amplitude of the mutual coupling coefficient from port H to port V. The phase drift of the mutual coupling coefficients from the H to V ports. The mutual fingerprint deviation metric is calculated using the aforementioned formula. T represents the currently monitored ambient temperature in degrees Celsius (°C). H represents the currently monitored ambient humidity in relative humidity percentages (%RH).

[0091] The technical benefits of this step are reflected in data dimensionality reduction and information enhancement, transforming high-dimensional, raw sensor data into a set of more informative and representative core features of health status, thus reducing the processing complexity of subsequent AI models. The innovative application of "mutually coupled fingerprints," with its proposed "mutually coupled fingerprint" and deviation metric MFDD, can sensitively reflect changes in the electromagnetic environment inside the feed source caused by factors such as structural micro-variations and connection degradation, especially exhibiting high sensitivity to polarization performance degradation, thereby improving diagnostic accuracy. The generated comprehensive feature vector F provides a standardized input format for the AI ​​diagnostic model, and through feature engineering, enhances the distinguishability between different health states (healthy, slightly degraded, severely faulty), and different fault modes.

[0092] VI. The steps for building and deploying the health assessment model are as follows:

[0093] The detailed process of health assessment includes collecting feature vectors of a large number of feed sources under different health conditions, including various typical failure modes, locations, and degrees, through electromagnetic simulation and accelerated aging tests in the laboratory. and The system then manually labels health scores and fault tags. Using these labeled datasets, one or more machine learning or deep learning models, such as SVM, random forest, XGBoost, small CNN, or MLP, are trained offline. The training objective is to learn the mapping from feature vector F to health scores, fault modes, and fault locations. The trained and optimized AI model, after processes such as quantization and pruning, is deployed to the feed's DCU (Digital Control Unit), edge computing units, or base station BBU (Base Station Bundle Unit) if computing power allows. During system operation, the processing unit extracts the real-time feature vectors... The data is fed into the deployed AI model. The AI ​​model performs inference calculations based on the patterns it has learned internally and outputs a diagnostic result for the current feed state.

[0094] The machine learning algorithms selected adopted a multi-model fusion approach, mainly including Support Vector Machine (SVM), Random Forest (RF), and Lightweight Neural Network (MLP). The SVM model uses a Radial Basis Function (RBF) kernel, and the kernel parameter γ is optimized through grid search; the Random Forest contains 100 decision trees with a maximum depth limit of 10 layers; the Multilayer Perceptron (MLP) contains two hidden layers with 64 and 32 neurons respectively, and the activation function is ReLU.

[0095] The training data consists of two parts: simulation data and laboratory test data. The simulation data uses the electromagnetic simulation software HFSS to simulate different types of damage scenarios, including minute deformations of one or a combination of oscillator arms B1-B4, cracks, etching defects, and local parameter changes in the dielectric substrate. For each simulated fault scenario, the corresponding comprehensive feature vector is recorded. Its fault labels and health scores. Laboratory accelerated aging test data are obtained by conducting high temperature and humidity, salt spray corrosion, vibration and other tests on actual antenna samples. Data is collected regularly and combined with manual inspection results to label the feature vector Flab and its health status.

[0096] in:

[0097] This is a comprehensive feature vector extracted when simulating various fault states using electromagnetic simulation software.

[0098] This study aims to collect data and extract a comprehensive feature vector by conducting accelerated aging tests on actual antenna samples in the laboratory at different aging or failure stages.

[0099] The training dataset contains 5,000 simulation samples and 2,000 laboratory test samples, covering four levels: healthy state, slight degradation, moderate failure, and severe failure. The health score is based on a scale of 0-100, where 90-100 indicates a healthy state, 70-89 indicates slight degradation, 50-69 indicates moderate failure, and 0-49 indicates severe failure.

[0100] The model was trained using 10-fold cross-validation, with the training and test sets split in an 8:2 ratio. The Adam optimizer was used during training, with a learning rate of 0.001, a batch size of 32, and 200 training epochs. To prevent overfitting, early stopping and dropout regularization were employed, with the dropout ratio set to 0.3.

[0101] The model deployment employs quantization and optimization strategies, performing INT8 quantization on the trained model, compressing the model size to 25% of its original size, and increasing inference speed by 4 times. The deployment platform can be either the feed's DCU when sufficient computing power is available or a connected edge computing unit. The edge computing unit uses an ARM Cortex-A72 quad-core processor with a clock speed of 1.8GHz and 4GB of memory, supporting accelerated machine learning inference.

[0102] During real-time diagnosis, the current comprehensive feature vector Input to a deployed AI model; model output includes:

[0103] The health score of the kth oscillator arm output by the AI ​​model is usually a value between 0 and 100, with a higher value indicating better health.

[0104] : The overall health score of the feed output by the AI ​​model.

[0105] The AI ​​model identifies the most likely fault mode or type of the current feed, such as "microcrack in B1 oscillator arm" or "abnormal increase in coupling between VH polarizations".

[0106] The fault location information provided by the AI ​​model, such as indicating which oscillator arm B1-B4, or which polarization V-Pol or H-Pol is causing the problem.

[0107] During actual operation of the antenna system, sensor data is collected in real time and the current integrated feature vector is extracted.

[0108] The confidence level of the output results is assessed through model ensemble. The diagnostic result is considered reliable when the consistency of the prediction results of the three models exceeds 80%.

[0109] The technological benefits of this step are reflected in intelligent diagnostics, enabling automatic and intelligent assessment of the feeder's health status. This replaces traditional methods relying on manual experience or periodic offline testing, improving diagnostic efficiency and accuracy. By outputting a quantified health score, maintenance personnel can intuitively understand the feeder's health status and set multi-level warning thresholds. It can not only determine whether a fault has occurred but also identify the type of fault and pinpoint the specific oscillator arm or polarization direction with a high probability, providing a basis for precise maintenance. Simultaneously, trend prediction capabilities enable predictive maintenance. The AI ​​model, through learning from a large amount of data, exhibits a certain degree of reliability against noise and minor disturbances and can adapt to environmental changes within a certain range.

[0110] VI. Perform the polarization intelligent reconfiguration steps, specifically as follows:

[0111] The detailed process of polarization intelligent reconstruction includes when the AI ​​model diagnoses that the performance of a certain polarization direction of the feed or the overall performance has significantly decreased and the health score is lower than a preset threshold. Furthermore, if conventional active impedance tuning on the base station side cannot fully recover, a polarization intelligent reconfiguration mechanism is triggered. The reconfiguration control logic typically begins when the base station BBU obtains the AI ​​diagnostic results. , And current "mutually coupled fingerprint" features such as MFDD and , Based on this information, the system identifies "harmful coupling paths" caused by faults and estimates the compensation coefficients required for cross-polarity cancellation, such as... , The goal is to counteract the cross-polarization components introduced by physical defects in the antenna. The system initiates an optimization algorithm based on the preset optimization objective. The optimization algorithm searches for and determines the optimal combination of complex weights for the digital domain transmitted signal within the allowed range. , or cross-compensation coefficient , The base station BBU applies the calculated optimized parameters to its digital signal processing link, dynamically adjusting the amplitude and phase of the raw baseband signal fed to the two physical polarization ports of the antenna. After the reconstruction is executed, the system continuously monitors key performance indicators (KPIs) and feed sensor data to evaluate the reconstruction effect, and performs iterative adjustments or re-triggers the reconstruction as needed.

[0112] When the overall health score of the feed Below the preset threshold At that time, the polarization intelligent reconstruction mechanism is activated. Preset threshold. The score is set according to the system performance requirements, and is usually 70 points, which indicates that the feeder performance has decreased significantly.

[0113] in: For the preset feed health score threshold, when the AI ​​diagnoses... When the value is below this level, the performance is considered to have degraded significantly, and a refactoring is required.

[0114] The prerequisites include that the two physical polarization ports of the feedhorn, V-Pol and H-Pol, are respectively connected to independent ports of the base station transceiver (TRX). The TRX's digital baseband processing unit (BBU) or intermediate frequency (IF) front-end must have the capability to independently, precisely, and dynamically adjust the amplitude and phase of the transmitted signals from the two polarization ports. That is, the complex weighting of the V-Pol signal can be controlled. Complex weights of H-Pol signals .

[0115] in, This is the complex weight applied to the signal at the V-polarized port. is the amplitude adjustment factor for the V-polarized port signal. e is the base of the natural logarithm. j is the imaginary unit ( =). This is the phase adjustment factor (usually in radians) for the V-polarized port signal. This is the complex weight applied to the signal at the H-polarized port. This is the amplitude adjustment factor for the H-polarized port signal. This is the phase adjustment factor (usually in radians) for the H-polarized port signal.

[0116] The identification of harmful coupling paths is based on the diagnostic results of the AI ​​model and the current "mutual coupling fingerprint" characteristics. The AI ​​model then uses the diagnostic results... , Based on the current "mutual coupling fingerprint" features, especially MFDD and its components, the main "harmful coupling paths" that lead to performance degradation, especially the decrease in polarization isolation (XPI), are identified. For example, if the diagnosis is that damage to the B1 oscillator arm causes abnormal coupling of V-Pol energy to the H-Pol direction, then the abnormal coupling path between B1 and H-Pol (composed of B2 / B4) is the harmful path.

[0117] The complex coefficients of cross-polarization leakage are estimated by analyzing the changes in the current cross-coupling coefficients relative to a reference value. Assuming the fault primarily affects the V-polarization, causing some of its energy EV_leak to leak into the H-polarization, the complex coefficients of the leakage are... Estimate using the formula:

[0118] ;

[0119] The detailed meanings of each parameter in this formula are as follows: The signal component leaking from the V-polarization path to the H-polarization path is represented by a complex number, which includes both amplitude and phase. (alpha_VH) is a complex leakage coefficient characterizing the leakage of the V-polarized signal into the H-polarized path. It describes the amplitude and phase relationship of the leaked signal relative to the original V-polarized intended signal. The original signal component intended to be emitted from the V-polarized path is represented by a complex number.

[0120] Similarly, if H-Pol is damaged, then... This coefficient can be analyzed. , Compared to , The changes are estimated by combining them with fault models. (alpha_HV) is a complex leakage or coupling coefficient that characterizes the signal transmitted in H-polarization, which is leaked or contributed to the V-polarization direction or received by the V-polarization port due to factors such as non-ideal coupling inside the antenna.

[0121] The compensation parameters are calculated using a cross-coupling compensation algorithm. To counteract this leakage, the excitation weights of the healthy port or both ports need to be adjusted. For example, to suppress leakage from V-Pol to H-Pol, the excitation of H-Pol is adjusted. This causes it to generate a compensation field that is inversely phase to the leakage field. More generally, the adjusted port excitation signal can be expressed as:

[0122] ;

[0123] ;

[0124] The detailed meanings of each parameter in this formula are as follows: The baseband signal is transmitted through the V-polarized port after compensation and adjustment. The baseband signal is transmitted through the H-polarized port after compensation and adjustment. To apply the main path complex weights to the original V-polarized signal, ,in For amplitude adjustment factor, This is the phase adjustment factor. To add complex weights to the main path of the original H-polarized signal, ,in For amplitude adjustment factor, This is the phase adjustment factor. This is the original, uncompensated V-polarized transmit baseband signal. This is the original, uncompensated H-polarized transmit baseband signal. The complex coefficients for cross-compensation applied to the H-polarized path signal, multiplied by the original H-polarized signal and the main path weight WH, constitute a compensation term superimposed on the V-polarized signal path. This compensation term aims to actively introduce an H-polarized source signal component with a specific amplitude and phase into the V channel to offset or reduce the influence of the H-polarized source signal. The harmful leakage or coupling effect described in the description of the path from the original H-polarized signal to the V-polarized signal. The complex coefficients for cross-compensation applied to the V-polarized path signal, multiplied by the original V-polarized signal and the main path weight WV, constitute a compensation term superimposed on the H-polarized signal path. This compensation term aims to actively introduce a V-polarized source signal component with a specific amplitude and phase into the H channel to offset or reduce the influence of the V-polarized source signal. The harmful leakage or coupling effect described in the description of the path from the original V-polarized signal to the H-polarized signal.

[0125] The reason and necessity for performing this cross-compensation is that when physical damage causes a decrease in the inherent isolation between polarizations, simple single-port amplitude and phase adjustment is insufficient to recover. This formula draws on the idea of ​​signal preprocessing or interference cancellation in MIMO. By actively cross-coupling the transmitted signal in the digital domain, the cross-polarization components introduced by physical defects in the antenna feed can be "cancelled" in advance before the signal leaves the antenna.

[0126] The amplitude and phase weights of the transmitted signals from the two polarization ports are adjusted through digital baseband processing. The complex weights of the V-polarization port are expressed as:

[0127] Where AV is the amplitude adjustment factor for the complex weight of the main path of the transmitted signal at the V-polarized port. This is the phase adjustment factor.

[0128] Where AH is the amplitude adjustment factor for the complex weight of the main path of the transmitted signal at the H-polarized port. This is the phase adjustment factor.

[0129] KPI-driven optimization search defines a comprehensive utility function U:

[0130] ;

[0131] The detailed meanings of each parameter in this formula are as follows: Let U be the overall utility function, and its value is a scalar representing the overall system performance under the current combination of reconfigured parameters. The optimization objective is to find the parameters that maximize U. k1 is the weighting coefficient of the first performance indicator, which is a positive value and is used to adjust the importance of SINR in the optimization objective. (or more accurately) ) represents the signal-to-interference-plus-noise ratio (SNR) achievable by the target user or link after reconstruction, expressed in decibels (dB). Maximizing this value helps improve communication quality. k2 is the weighting coefficient for the second performance metric, cross-polarization power. It is a positive value; multiplying by a negative sign indicates a desire to minimize this term. The estimated total cross-polarization leakage power is expressed in watts (W) or decibels (dBm). Reducing this term helps improve polarization purity. k3 is the weighting coefficient for the deviation of the third performance indicator, health; it is a positive value, and multiplying by a negative sign indicates a desire to minimize this term. The overall health score of the feed source diagnosed by the current AI model. The desired baseline or target value for feed health, such as a pre-failure health score or an acceptable minimum health level, | | Indicates the gap between the current health status and the target.

[0132] The reason and necessity for implementing this utility function lies in the fact that actual reconfiguration requires trade-offs among multiple potentially conflicting objectives. This formula provides a framework that unifies desired communication performance (SINR), the antenna's own polarization purity (Pcross-pol), and the degree of deviation from the original healthy state (representing possible beam distortion) into a single optimization objective. By adjusting the weights ki, the reconfiguration strategy can be flexibly adjusted according to different scenarios, such as coverage priority, capacity priority, and interference suppression priority.

[0133] The optimization algorithm employs Particle Swarm Optimization (PSO) to search for the optimal combination of complex weights. The control system, typically located at the base station BBU, receives diagnostic information and current S-parameters from the feed MCU or edge computing unit and runs optimization algorithms such as hill climbing, simulated annealing, PSO, or gradient-based optimization methods to search for the optimal combination of complex weights. or compensation coefficient The goal is to maximize the utility function U. During optimization, adjustable parameters need to be considered. , , , The actual dynamic range and accuracy limitations.

[0134] The PSO algorithm parameters are set as follows: particle swarm size of 30, maximum number of iterations of 100, inertia weight of 0.7, and learning factors c1=c2=2.0. The algorithm updates particle positions and velocities in each iteration, gradually converging to the optimal weight combination through guidance from both global and individual optima.

[0135] The application of optimized weighting parameters is achieved through the base station's digital signal processing (BBU). The base station BBU applies the calculated optimized complex weights or compensation coefficients to the BBU to adjust the transmitted signals at the two physical polarization ports. After reconstruction, the system continuously monitors KPI and feed sensor data to evaluate the reconstruction effect. If the effect is unsatisfactory or the condition continues to deteriorate, it may attempt reconstruction again or trigger a higher-level alarm. The base station BBU receives the weighting parameters calculated by the optimization algorithm and applies them to the digital predistortion (DPD) unit and beamforming unit. Digital signal processing includes: complex weighting of the baseband signal, cross-coupling compensation processing, digital up-conversion, and power amplifier predistortion.

[0136] The technical benefits of this step are reflected in adaptive performance recovery. When the feed source suffers physical damage or performance degradation, the polarization of the transmitted signal is intelligently adjusted to actively compensate for antenna defects, thereby restoring or maintaining key performance indicators of the communication link to a certain extent. Precise cross-polarization cancellation effectively suppresses inter-polarization interference caused by feed source failures, improving the performance of the MIMO system. This allows the antenna system to continue providing service even after certain types of failures, postponing the need for physical repair or replacement and reducing maintenance costs. It improves the robustness and service continuity of the communication system in the face of antenna component failures, reducing service interruptions caused by antenna problems. The introduction of the utility function U allows the reconfiguration strategy to be flexibly adjusted according to current network needs, such as coverage priority or capacity priority, achieving more refined performance management.

[0137] VII. Follow the alarm and maintenance guidelines to execute the procedures as follows:

[0138] The detailed workflow for alarms and maintenance guidelines includes continuous system monitoring of the overall health score of the feed source diagnosed by AI. And the restructured KPIs. When The alarm value remains below the preset critical alarm threshold. If the polarization intelligent reconfiguration fails to maintain key KPIs above acceptable levels, or if the AI ​​model predicts a serious feedhorn failure within a short period, the system automatically triggers an alarm mechanism. The system generates a detailed alarm report, including: the unique identifier of the faulty antenna, its geographic location information (if GPS is integrated), the alarm occurrence time, the alarm level, detailed AI diagnostic results, a summary of the sensor's raw data at the time the alarm was triggered, and its feature vector. The alarm report includes the attempted refactoring strategies and their effectiveness evaluation, as well as the preliminary fault cause analysis provided by the system based on the fault mode. This alarm report is submitted to the upper-level network operations and maintenance management system (OMS) via the network interface. OMS receives and parses the alarm information, presents it to operations and maintenance personnel, and can automatically generate maintenance work orders according to preset rules.

[0139] The alarm triggering mechanism is based on multiple conditions: when the AI-diagnosed overall health score of the feed source... Continuously below the critical alarm threshold More than 5 minutes; when the polarization intelligent reconfiguration is executed, the key KPIs still cannot be maintained above the acceptable level, such as the SINR dropping by more than 3dB; when the AI ​​model predicts that the feed source will experience a serious failure within the next 24 hours, the health score prediction value is less than 30 points.

[0140] in: The preset critical alarm threshold for the overall health score of the feed source, when When the value is below this, it indicates that the feed source is in very poor condition and requires immediate attention or maintenance.

[0141] Alarm information is generated using a structured report format, including the following: unique antenna identifier, GPS location information (latitude and longitude coordinates), alarm timestamp (UTC format), alarm level (1-5, with level 5 being the most severe), and detailed AI diagnostic results. , , , A snapshot of the sensor's raw data when the alarm is triggered, and the current feature vector. The complete numerical values, the attempted refactoring strategies and their effectiveness evaluation, and the preliminary fault cause analysis given by the system based on the fault mode.

[0142] The fault cause analysis employs a combination of a rule engine and a knowledge graph. The rule engine contains 150 expert-based rules, covering the characteristic patterns and possible causes of common fault modes. The knowledge graph constructs the relationships between antenna components, fault types, and environmental factors, supporting inference analysis. For example, when the current amplitude deviation of the B1 vibrator arm is detected to be greater than 20%, and the VH polarization mutual coupling coefficient increases by more than 15%, and the ambient humidity exceeds 85%, the system infers that "the B1 vibrator arm may have degraded insulation performance due to moisture intrusion, causing abnormal current and enhanced polarization coupling."

[0143] Alarm information reporting is implemented via SNMP protocol and RESTful API. SNMP version 3 is used, supporting encryption and authentication to ensure secure transmission of alarm information. The RESTful API uses HTTPS protocol and supports data exchange in JSON format. The reporting target is the Network Management System (OMS), supporting multi-level reporting and cascading alarms.

[0144] Maintenance guidance is generated based on expert systems and decision tree algorithms. Based on alarm information, the OMS provides maintenance personnel with precise fault antenna location and preliminary fault cause analysis, guiding on-site maintenance work such as checking specific vibrator arms, feeder connections, and removing foreign objects, thus shortening fault diagnosis and repair time. The system uses fault location information... It automatically generates detailed maintenance guidance documents, including: a precise description of the fault location, recommended inspection steps, a list of required tools and spare parts, safety precautions, and estimated repair time. For example, for a B1 vibrator arm fault, the maintenance guide includes: "1. Turn off the antenna power; 2. Remove the radome; 3. Inspect the surface of the B1 vibrator arm for physical damage; 4. Use a multimeter to measure the DC resistance of the B1 vibrator arm; 5. Check the connection status of the B1 vibrator arm to the feed network; 6. If damage is found, replace the B1 vibrator arm assembly."

[0145] The technical benefits of this step are reflected in timely and proactive alarms, enabling early detection and timely reporting of faults, preventing the accumulation of problems that could lead to more serious system failures or prolonged service quality degradation. The detailed diagnostic information and preliminary cause analysis provided greatly help maintenance personnel quickly locate problematic antennas and fault points, shortening troubleshooting time. It provides clear guidance for on-site maintenance work, such as checking specific vibrator arms and feeder connections, improving maintenance efficiency and reducing the heavy reliance on the experience of maintenance personnel. The accumulated alarm and diagnostic data can be used to analyze common antenna fault patterns and trends, providing data support for spare parts management and the development of preventative maintenance plans, optimizing overall maintenance strategies. Maintenance is triggered by alarms, and the maintenance results can be fed back through system monitoring, forming a closed loop of fault management and performance maintenance.

[0146] Through the implementation of the above steps, the performance maintenance method for the high-gain dual-polarized parabolic antenna system of the present invention can achieve refined and intelligent health status monitoring and early fault warning of the feed element. Furthermore, it maintains the quality and availability of the communication link as much as possible through intelligent reconfiguration when performance degradation occurs, thus improving the resilience and adaptability of the antenna system. This method, through real-time monitoring, intelligent diagnosis, and adaptive reconfiguration, ensures that the antenna can still maintain the availability and quality of the communication link to the maximum extent even when feed element performance degradation or failure is possible. This significantly improves the resilience and adaptability of the antenna system, providing strong protection for the reliability and quality of service of wireless communication systems.

Claims

1. A method for maintaining the performance of a high-gain dual-polarized parabolic antenna system, characterized in that, A high-gain dual-polarized parabolic antenna system is provided, comprising a parabolic reflector and a feed source, wherein the feed source is disposed at the focal or near-focal region of the parabolic reflector; the feed source includes a printed circuit board (PCB) on which metal oscillator elements are formed by etching; the metal oscillator elements include at least two sets of orthogonally arranged oscillators, forming radiation in two orthogonal polarization directions; each oscillator of the metal oscillator elements integrates a low-frequency radiating part for a first frequency band and a high-frequency radiating part for a second frequency band, wherein the first frequency band and the second frequency band correspond to the 900MHz band and the 1800MHz band, respectively; The feed source radiates dual-polarized electromagnetic waves through the metal oscillator unit, and the electromagnetic waves are reflected by the parabolic reflector to form a high-gain directional beam. The performance preservation method includes the following steps: Sensor deployment steps: Integrate current monitoring sensors, port characteristic monitoring sensors, and environmental parameter sensors on the feed unit; Data acquisition configuration steps: Configure the data acquisition unit, establish connection with each sensor, and set the data acquisition period and parameters; Data acquisition and processing steps: The data acquisition unit acquires the output signals of each sensor at a set period, and filters and digitizes the acquired signals; Data output steps: Transmit the processed data to an external processing unit or store it in a local storage medium via a communication interface; The sensor deployment step provides a signal source basis for the data acquisition configuration step. The parameter setting in the data acquisition configuration step controls the execution timing of the data acquisition and processing steps. The output results of the data acquisition and processing steps are transmitted externally through the data output step. Also includes: Feed source health status feature parameters are extracted from the output data of the data acquisition and processing. These feature parameters include: The deviation of the current amplitude of each metal oscillator arm is calculated by the absolute value of the difference between the current monitored current amplitude and the reference current amplitude. The current phase deviation of each metal oscillator arm is calculated by the absolute value of the difference between the current monitored current phase and the reference current phase. Extract the percentage change in amplitude of the mutual coupling coefficient between polarization ports and the phase drift of the mutual coupling coefficient; The mutual coupling fingerprint deviation metric is calculated based on the percentage change in the amplitude of the mutual coupling coefficient and the phase drift. The current amplitude deviation, current phase deviation, mutual coupling coefficient variation parameter, mutual coupling fingerprint deviation metric value, and environmental parameters are combined to construct a comprehensive feature vector; The mutual coupling fingerprint deviation metric (MFDD) is a comprehensive quantitative indicator of the degree to which the feed mutual coupling state deviates from the baseline. A larger value indicates a more severe deviation. Its calculation uses a weighted synthesis method. ； In the formula, This is a weighting factor for the amplitude change of the mutual coupling coefficient, with a value ranging from 0 to 1, used to adjust the importance of amplitude change in the comprehensive evaluation; This is a weighting factor for the phase change of the mutual coupling coefficient, ranging from 0 to 1, used to adjust the importance of phase change in the overall evaluation. ; This is the absolute value of the percentage change in the mutual coupling coefficient amplitude from the V-polarized port to the H-polarized port; This is the absolute value of the percentage change in the mutual coupling coefficient amplitude from the H-polarized port to the V-polarized port; The absolute value of the phase drift of the mutual coupling coefficient from the V-polarized port to the H-polarized port, in degrees (°) or radians (rad). The absolute value of the phase drift of the mutual coupling coefficient from the H-polarized port to the V-polarized port, in degrees (°) or radians (rad). This is the phase normalization constant, taken as 180 degrees or π radians, used to normalize the phase deviation to a comparable range.

2. The method for maintaining the performance of the high-gain dual-polarized parabolic antenna system according to claim 1, characterized in that, The metal oscillator unit includes a first polarized oscillator group, which is composed of a first metal oscillator arm and a second metal oscillator arm symmetrically arranged therewith. The first metal oscillator arm and the second metal oscillator arm together form a radiation in a polarization direction.

3. The method for maintaining the performance of the high-gain dual-polarized parabolic antenna system according to claim 2, characterized in that, The metal oscillator unit further includes a second polarized oscillator group, which is composed of a third metal oscillator arm and a fourth metal oscillator arm symmetrically arranged therewith. The second polarized oscillator group is arranged on the PCB plane at a 90-degree rotation relative to the first polarized oscillator group, forming a polarization direction radiation orthogonal to the first polarized oscillator group.

4. The method for maintaining the performance of the high-gain dual-polarized parabolic antenna system according to claim 3, characterized in that, Each of the first, second, third, and fourth metal oscillator arms includes a low-frequency radiating part and a high-frequency radiating part. The high-frequency radiating part is nested or integrated within or near the structure of the low-frequency radiating part. The low-frequency radiating part is an arm-shaped structure with a relatively long length and a relatively wide width, while the high-frequency radiating part is an arm-shaped structure with a relatively short length and a relatively narrow width.

5. The method for maintaining the performance of the high-gain dual-polarized parabolic antenna system according to claim 4, characterized in that, The feed source also includes a guide plate, which is formed on the PCB by an etching process. The guide plate is located in front of the main radiation direction of the high-frequency radiating part and is used to expand the operating bandwidth of the 1800MHz band and increase the gain value of the band.

6. The method for maintaining the performance of the high-gain dual-polarized parabolic antenna system according to claim 5, characterized in that, The antenna system has a voltage standing wave ratio (VSWR) of less than or equal to 1.7 in the 900MHz to 1800MHz frequency band.

Images