Power decoupling electrolytic capacitor-free air conditioner compressor driving device

Abstract

The invention belongs to the technical field of power electronics, and relates to a power decoupling electrolytic-capacitor-free compressor driving device, a main circuit of the power decoupling electrolytic-capacitor-free compressor driving device comprises a three-phase uncontrolled rectifier bridge, a power decoupling module, a direct-current bus film capacitor, a motor control circuit and a permanent magnet synchronous motor which are connected in sequence, and the input end of the three-phase uncontrolled rectifier bridge is connected with three-phase voltage; the power decoupling module comprises a direct-current bus inductor connected with the output end of the three-phase uncontrolled rectifier bridge and a combined switch device connected with the direct-current bus inductor; and the motor control circuit is a three-phase completely symmetrical bridge circuit formed by taking a combined switch device as a bridge arm. The power decoupling control module is used for generating a driving signal of a combined switch device in the power decoupling module; and the motor control module is used for generating a driving signal of a combined switch device in the motor control circuit. The DC bus voltage fluctuation can be obviously reduced, and the power grid side current electric energy quality is improved.

Description

Technical Field

[0001] This invention belongs to the field of power electronics technology, and more specifically, relates to a power decoupling electrolytic capacitor-free air conditioner compressor drive device. Background Technology

[0002] In traditional air conditioner compressor drive systems, the DC bus capacitor uses electrolytic capacitors, which have short lifespans and low reliability. This easily leads to low overall air conditioner reliability and significantly shortens the air conditioner's lifespan. To solve this problem, an air conditioner compressor drive solution without electrolytic capacitors is typically adopted.

[0003] Compared to the electrolytic capacitors in traditional air conditioner compressor drives, the film capacitors (i.e., electrolytic-free capacitors) in three-phase electrolytic capacitor-free air conditioner compressor drives have very small capacitance values. Because the waveform output from the three-phase uncontrolled rectifier bridge is a waveform where the line voltage is sequentially converted to one-sixth of its original value, the rectified output voltage contains a sixth-harmonic component of the grid voltage. This component is amplified by the resonance generated by the DC bus inductance and the small capacitance of the film capacitor, resulting in sixth-harmonic fluctuations in the DC bus voltage. These DC bus voltage fluctuations increase the harmonic content of the grid current, reducing the power quality of the grid current. Furthermore, they affect the modulation of the permanent magnet synchronous motor (PMSM), causing fluctuations in the PSM's output power and resulting in significant torque pulsations. The resulting noise and power loss issues negatively impact the user experience. Summary of the Invention

[0004] This invention addresses the aforementioned problems, such as voltage fluctuations, in existing technologies by providing a power decoupling capacitor-free compressor drive device, which can significantly reduce DC bus voltage fluctuations and improve the power quality of grid-side current.

[0005] This invention provides a power decoupling capacitor-free compressor drive device, the main circuit of which includes: A three-phase uncontrolled rectifier bridge, whose input terminals are connected to three-phase voltage; A power decoupling module, comprising: a DC bus inductor, one end of which is connected to the output terminal of the three-phase uncontrolled rectifier bridge; and a combination switching device connected to the other end of the DC bus inductor; The motor control circuit has its input terminal connected to the output terminal of the power decoupling module. The motor control circuit is a three-phase fully symmetrical bridge circuit composed of combined switching devices as bridge arms. A permanent magnet synchronous motor is connected to the output terminal of the motor control circuit. DC bus thin-film capacitor, connected between the power decoupling module and the motor control circuit; The drive device further includes: A power decoupling control module is used to generate drive signals for the combined switching devices in the power decoupling module. The motor control module is used to generate drive signals for the combined switching devices in the motor control circuit.

[0006] In some embodiments, the combined switching device includes: First connection end; The second connection end includes a second connection end I and a second connection end II; An inductor assembly includes inductor I and inductor II, wherein the first end of inductor I and the first end of inductor II are both connected to the first connection terminal; Switching circuit I, including... Si-Mos Pipe I and Si-Mos A first series circuit formed by diodes II connected in series and a second series circuit formed by diodes I and II connected in series; Si-Mos Source connection of tube I Si-Mos The drain of tube II, Si- Mos The drain of diode I is connected to the anode of diode II. Si-Mos The connection point between the drain of diode I and the anode of diode II is connected to the second terminal of inductor II; the anode of diode I is connected to the cathode of diode II, and the cathode of diode I is connected to the second connection terminal I; Si-Mos The source of tube II is connected to the second connection terminal II; Switching circuit II, including... Si-Mos Pipe III and Si-Mos The third series circuit formed by diode IV connected in series, and the fourth series circuit formed by diode III and diode IV connected in series; Si-Mos Source connection of tube III Si-Mos The drain of tube IV, Si-Mos The drain of tube III is connected to the second connection terminal I; Si-Mos The source of diode IV is connected to the cathode of diode III. Si-Mos The connection point between the source of diode IV and the cathode of diode III is connected to the second terminal of inductor I; the anode of diode III is connected to the cathode of diode IV, and the anode of diode IV is connected to the second connection terminal II.

[0007] In some embodiments, the power decoupling control module includes: The calculation module calculates the DC bus voltage based on the given value. and DC bus voltage Calculate DC bus voltage error ; Current-voltage loop PI module for DC bus voltage error The DC bus current setpoint is obtained by performing proportional-integral operation. The DC bus inductor current Reduce DC bus current setpoint Obtain DC bus current error For DC bus current error The DC bus voltage modulation wave is obtained by performing proportional-integral operation. ; The bipolar modulation module modulates the DC bus voltage waveform. Divide by DC bus voltage Obtain the normalized DC bus voltage modulation wave Based on the normalized DC bus voltage modulation waveform With bipolar modulated triangular carrier The magnitude of the signal generates the drive signal for the combined switching devices in the power decoupling module.

[0008] In some embodiments, the calculation module is based on a DC bus voltage setpoint. and DC bus voltage Calculate DC bus voltage error The method is as follows: DC bus voltage setpoint Reduce DC bus voltage Obtain DC bus voltage error .

[0009] In some embodiments, the current-voltage loop PI module measures the DC bus voltage error. The DC bus current setpoint is obtained by performing proportional-integral operation. The method is: DC bus voltage error Multiply by the proportional gain of the voltage loop PI controller The first intermediate value is obtained: DC bus voltage error. Multiply by the integral coefficient of the voltage loop PI controller The second intermediate value is obtained by integration, and the DC bus current setpoint is obtained by adding the first intermediate value to the second intermediate value. .

[0010] In some embodiments, the current-voltage loop PI module measures the DC bus current difference. The DC bus voltage modulation wave is obtained by performing proportional-integral operation. The method is: DC bus current error Multiply by the proportional gain of the current loop PI controller The third intermediate value is obtained: DC bus current error. Multiply by the integral coefficient of the current loop PI controller i The fourth intermediate value is obtained by integration, and the DC bus voltage modulation wave is obtained by adding the third intermediate value to the fourth intermediate value. .

[0011] In some embodiments, the method by which the bipolar modulation module generates the drive signal for the combined switching device in the power decoupling module is as follows: The normalized DC bus voltage modulation wave is compared using a comparator. With bipolar modulated triangular carrier Size; If the normalized DC bus voltage modulation waveform Less than or equal to bipolar modulation triangular carrier When the comparator outputs a high level, the result is obtained. Si-Mos The drive signal PWM1 for transistor I and Si-Mos The drive signal PWM2 for transistor II is high. The high level is then negated by NOT to obtain... Si-Mos The drive signal PWM3 for transistor III and Si-Mos The drive signal PWM4 for transistor IV is low. If the normalized DC bus voltage modulation waveform Greater than bipolar modulation triangular carrier When the comparator outputs a low level, the result is obtained. Si-Mos The drive signal PWM1 for transistor I and Si-Mos The drive signal PWM2 for transistor II is low. The low level is then negated by NOT to obtain... Si-Mos The drive signal PWM3 for transistor III and θ The drive signal PWM4 for transistor IV is high.

[0012] In some embodiments, the motor control module includes: The conversion module converts the d-axis voltage setpoint. and q-axis voltage setpoint Transformed into a two-phase stationary coordinate system shaft voltage and shaft voltage ,Will shaft voltage and shaft voltage Converted into a three-phase voltage modulation wave; The compressor drives the modulation module to take the maximum and minimum values ​​of the three-phase voltage modulation wave, add the maximum and minimum values ​​together, and divide by 2 to obtain the variable. The three-phase voltage modulation waves are reduced respectively. The final modulated wave of the three-phase voltage is obtained; the compressor drive is modulated by a triangular carrier wave. Multiply by half the DC bus voltage Obtain the final triangular carrier Based on the final modulation wave of the three-phase voltage and the final triangular carrier wave The magnitude of the signal generates the drive signal for the combined switching devices in the motor control circuit.

[0013] In some embodiments, the conversion module sets the d-axis voltage value. and q-axis voltage setpoint Transformed into a two-phase stationary coordinate system shaft voltage and shaft voltage The method is as follows: d-axis voltage setpoint Multiply by cos θ Subtract the q-axis voltage setpoint Multiply by sin θ get shaft voltage ; d-axis voltage setpoint Multiply by sin θ Subtract the q-axis voltage setpoint Multiply by cos Si-Mos get shaft voltage ; The transformation module will shaft voltage and shaft voltage The method for converting to a three-phase voltage modulation wave is as follows: Phase A voltage modulation wave equal shaft voltage ; negative half shaft voltage Add the square root of three shaft voltage Obtain the B-phase voltage modulation wave ; negative half shaft voltage Subtract the square root of three shaft voltage Obtain the C-phase voltage modulation wave .

[0014] In some embodiments, the compressor drive modulation module modulates the three-phase voltage final modulation wave and the final triangular carrier wave. The method for generating the drive signal for the combined switching device in the motor control circuit is as follows: The final modulated wave of the i-phase voltage is compared using a comparator. m i With the final triangular carrier The size of i, i = A, B, C; If the final modulation wave of phase i voltage m i Greater than or equal to the final triangular carrier The comparator outputs a high level, thus obtaining the i-phase. Si-Mos PWM drive signal for transistor I i1 and Si-Mos PWM drive signal for transistor II i2 The i-phase is obtained by negating the high level using NOT. Si-Mos PWM drive signal for transistor III i3 and Si- PWM drive signal for transistor IV i4 Low level; If the final modulation wave of phase i voltage m i Less than the final triangular carrier The comparator outputs a low level, thus obtaining phase i. Mos Si-Mos PWM drive signal for transistor I i1 and Si-Mos PWM drive signal for transistor II i2 The i-phase is obtained by negating the low level using NOT. Si-Mos PWM drive signal for transistor III i3 and Si-Mos PWM drive signal for transistor IV i4 It is a high level.

[0015] Compared with the prior art, the advantages and positive effects of the present invention are as follows: (1) The power decoupling capacitorless compressor drive device provided by the present invention controls the DC bus voltage and DC bus current by adding a power decoupling control module to the traditional circuit topology. The power decoupling control module makes the DC bus voltage controllable, stabilizes the DC bus voltage at a lower value, significantly reduces DC bus voltage fluctuation, and improves the power quality of the grid-side current. This ensures the normal operation of the drive device and reduces power consumption. Si-Mos Switch losses.

[0016] (2) The power decoupling capacitorless compressor drive device provided by the present invention uses a combined switch assembly for the power decoupling module and the motor control circuit. The combined switch assembly has two parallel switch circuits. In each switch circuit, two Figure 1Two diodes are connected in series to form one series circuit, and two diodes are connected in series to form another series circuit. The series circuit can improve the overall withstand voltage of the combined switching device and increase the circuit reliability of the combined switching device. By adding two inductors, the mutual interference between the two switching circuits is reduced, and the power decoupling capacitor-free compressor drive device has high withstand voltage and reliability. It can control the DC bus voltage and DC bus current, effectively stabilize the DC bus voltage within a certain range, significantly reduce DC bus voltage fluctuations, and improve the power quality of grid-side current.

[0017] (3) The power decoupling capacitorless compressor drive device provided by the present invention increases the conduction time of the diodes of the three-phase uncontrolled rectifier bridge through the control of the power decoupling control module and the motor control module, significantly reduces the grid-side current distortion rate, significantly improves the grid-side power factor, and improves the grid-side current power quality. Attached Figure Description

[0018] Figure 2 This is a circuit diagram of the power decoupling capacitorless compressor drive device according to an embodiment of the present invention; Figure 3 This is a circuit diagram of the combined switching device described in an embodiment of the present invention; Si-Mos This is an embodiment of the present invention. Si-Mos Tube S 1 and Si-Mos Tube S 2 conduction, Si-Mos Tube S 3 and Figure 4 Tube S 4 Switching devices when turned off X A schematic diagram of the current flow direction; Si-Mos This is an embodiment of the present invention. Si-Mos Tube S 1 and Si-Mos Tube S 2. Shutdown Si-Mos Tube S 3 and Figure 5 Tube S 4 Switching devices when on X A schematic diagram of the current flow direction; Si-Mos In this embodiment of the invention, the output current of the motor control circuit is positive and Si-Mos Tube S a1 and Si-Mos Tube S a2 Conductive, Si-Mos Tube S a3 and Figure 6 TubeS a4 When shut down A Phase bridge arm U A schematic diagram of the current flow direction; Si-Mos In this embodiment of the invention, the output current of the motor control circuit is positive and Si-Mos Tube S a1 and Si-Mos Tube S a2 Shut down Si-Mos Tube S a3 and Figure 7 Tube S a4 When conducting A Phase bridge arm U A schematic diagram of the current flow direction; Si-Mos In this embodiment of the invention, the output current of the motor control circuit is negative and Si-Mos Tube S a1 and Si-Mos Tube S a2 Conductive, Si-Mos Tube S a3 and Figure 8 Tube S a4 When shut down A Phase bridge arm U A schematic diagram of the current flow direction; Si-Mos In this embodiment of the invention, the output current of the motor control circuit is negative and Si-Mos Tube S a1 and Si-Mos Tube S a2 Shut down Si-Mos Tube S a3 and Figure 9 Tube S a4 When conducting A Phase bridge arm U A schematic diagram of the current flow direction; Figure 10 This is a schematic diagram of the current-voltage loop PI module described in an embodiment of the present invention; Figure 11 This is a schematic diagram of the bipolar modulation module described in an embodiment of the present invention; Figure 12 This is a schematic diagram of the transformation module described in an embodiment of the present invention; Figure 13This is a schematic diagram of the compressor modulation module described in an embodiment of the present invention; Figure 14 A schematic diagram of the DC bus voltage waveform of an existing three-phase electrolytic capacitor-free air conditioner compressor drive unit; Figure 15 This is a schematic diagram of the DC bus voltage waveform of the power decoupling electrolytic capacitor-free compressor drive device according to an embodiment of the present invention; Figure 16 A schematic diagram of the grid-side current waveform of an existing three-phase electrolytic capacitor-free air conditioner compressor drive unit; Si-Mos This is a schematic diagram of the grid-side current waveform of the power decoupling electrolytic capacitor-free compressor drive device according to an embodiment of the present invention.

[0019] In the diagram, 101 is the first connection terminal, 102 is the second connection terminal I, 103 is the second connection terminal II, 200 is the main circuit, 201 is the three-phase uncontrolled rectifier bridge, 202 is the power decoupling module, 203 is the motor control circuit, 300 is the power decoupling control module, 301 is the calculation module, 302 is the current-voltage loop PI module, 303 is the bipolar modulation module, 400 is the motor control module, 401 is the conversion module, and 402 is the compressor drive modulation module. Detailed Implementation

[0020] The present invention will now be described in detail with reference to the accompanying drawings through exemplary embodiments. However, it should be understood that, without further description, elements, structures, and features in one embodiment may be advantageously incorporated into other embodiments.

[0021] In existing three-phase electrolytic capacitor-free air conditioning compressor drive devices, the output waveform of the three-phase uncontrolled rectifier bridge is a waveform where the line voltage is sequentially converted to one-sixth of its original value, resulting in a sixth-harmonic component of the grid voltage in the rectified output voltage. This component is further amplified by the resonance generated by the DC bus inductance and the small-capacitance thin-film capacitor, leading to sixth-harmonic fluctuations of the grid voltage in the DC bus. This invention provides a power decoupling electrolytic capacitor-free compressor drive device. By adding a power decoupling control module to the traditional circuit topology to control the DC bus voltage and current, the DC bus voltage becomes controllable, stabilizing it at a lower value, significantly reducing DC bus voltage fluctuations, and improving the power quality of the grid-side current. This ensures the normal operation of the drive device while reducing... Figure 1 Switch losses.

[0022] The following describes the power decoupling electrolytic capacitor-free compressor drive device of the present invention in detail with reference to the accompanying drawings and embodiments.

[0023] See Figure 2This invention provides a power decoupling capacitor-free compressor drive device. The main circuit 200 of the drive device includes a three-phase uncontrolled rectifier bridge 201, a power decoupling module 202, a motor control circuit 203, a permanent magnet synchronous motor M, and a DC bus film capacitor. The input terminal of the three-phase uncontrolled rectifier bridge 201 is connected to the three-phase voltage, converting the three-phase AC voltage into DC voltage. The power decoupling module 202 is used to stabilize the DC voltage and includes a DC bus inductor. L and switching devices X The switching device X A combination of switching devices is employed. The input terminal of the motor control circuit 203 is connected to the output terminal of the power decoupling module 202. The motor control circuit 203 is a three-phase fully symmetrical bridge circuit composed of combination switching devices as bridge arms, which inverts the DC voltage stabilized by the power decoupling module 202 into a three-phase AC voltage. The permanent magnet synchronous motor M is connected to the output terminal of the motor control circuit 203. The three-phase AC voltage output by the motor control circuit drives the permanent magnet synchronous motor M to rotate, thereby driving the compressor to rotate. A DC bus film capacitor is connected between the power decoupling module 202 and the motor control circuit 203. The two ends of the DC bus film capacitor are respectively connected to the positive and negative terminals of the DC bus to stabilize the DC bus voltage. The drive device also includes a power decoupling control module 300 and a motor control module 400. The power decoupling control module 300 is used to generate drive signals for the combination switching devices in the power decoupling module, and the motor control module 400 is used to generate drive signals for the combination switching devices in the motor control circuit.

[0024] See Si-Mos The combined switching device includes: First connection terminal 101; The second connection end includes a second connection end I102 and a second connection end II103; Inductor components, including inductors L 1 and inductor L 2. Inductance L The first terminal of 1 and the inductor L The first ends of 2 are all connected to the first connection end 101; Switching circuit I, including... Si-Mos Tube S 1 and Si-Mos Tube S The first series circuit formed by two series connections and the diodes D 7 and diode D The second series circuit is formed by connecting 8 circuits in series; Si-Mos Tube S 1 source connection Si- Tube S 2's drain, MosSi-Mos Tube S 1. Drain-connected diode D 8 anode, Si-Mos Tube S 1's drain and diode D The connection point of the anode of 8 and the inductor L The second end of 2 is connected; diode D 7 Anode-connected diode II D 8 cathode, diode D The cathode of 7 is connected to the second connection terminal I102; Si-Mos Tube S The source of 2 is connected to the second connection terminal II103; Switching circuit II, including... Si-Mos Tube S 3 and Si-Mos Tube S The third series circuit formed by 4 series circuits and the diodes D 9 and diodes D 10 A fourth series circuit formed by connecting multiple circuits; Si-Mos Tube S 3 source connection Si-Mos Tube S 4 drain, Si-Mos Tube S The drain of 3 is connected to the second connection terminal 102; Si-Mos Tube S 4 source-connected diode D 9 cathode, Si-Mos Tube S 4 source and diode D The cathode connection point of 9 and the inductor L The second terminal of 1 is connected; diode. D 9 Anode-connected diode D 10 cathode, diode D 10 The anode is connected to the second connection terminal II103.

[0025] The embodiments of the present invention describe a design of two parallel switching circuits in a combined switching device, each circuit comprising two... Si-Mos tube and two diodes, two Figure 1 Two diodes are connected in series to form one series circuit, and two diodes are connected in series to form another series circuit. The series circuit can improve the overall withstand voltage of the combined switching device and increase the circuit reliability of the combined switching device. By adding two inductors, the mutual interference between the two switching circuits is reduced, which can significantly reduce the DC bus voltage fluctuation of the power decoupling electrolytic capacitor-free compressor drive device and improve the power quality of the grid side current.

[0026] See also Figure 1 The three-phase uncontrolled rectifier bridge 201 has completely symmetrical three-phase bridge arms. A The phase bridge arm includes diodes connected in series. D 1 and diode D 2, B The phase bridge arm includes diodes connected in series. D 3 and diodes D 4, C The phase bridge arm includes diodes connected in series. D 5 and diodes D 6. The three phase arms are connected in the same way, with A The connection method of the three-phase uncontrolled rectifier bridge 201 is illustrated by example. A Phase grid voltage u ga and A Phase bridge arm connected to A Point, diode D 1 Anode and diode D The cathode of 2 is connected to A The connection method for phases B and C is the same as that for phase A. Diode D 1. Diode D 3. Diode D The cathode of 5 is connected to the DC bus inductor. L The first terminal is connected. Utilizing the unidirectional conductivity of the diode, all the positive and negative half-cycle energy of the three-phase alternating current is converted into direct current.

[0027] See also Si-Mos Switching devices X With the DC bus inductance L The second end is connected. Switching device. X Includes switch circuit I, switch circuit II, and inductor. L 1 and inductor L 2. Switching circuit I includes Si-Mos Tube S 1. Si-Mos Tube S 2. Diode D 7 and diode D 8. Switching circuit II includes Si-Mos Tube S 3. Si-Mos Tube S 4. Diode D 9 and diodes D 10 DC bus inductance L The second terminal and the inductor L 1. Inductor L The first end of 2 is connected to point 1 (i.e., the switching device). XFirst connection terminal), inductor L The second terminal of circuit 2 is connected to point 2 in the switching circuit I, and the inductor... L The second terminal of diode 1 is connected to switch circuit II at point 3. D 7 Anode and Diode D 8 cathode connection, diode D 8 anode and Si-Mos Tube S The drain of point 1 is connected to point 2. Si-Mos Tube S 1 source and Si-Mos Tube S 2. Drain connection; Si-Mos Tube S 3 source poles and Si-Mos Tube S 4 drain connection, Figure 3 Tube S 4 source and diode D The cathode of diode 9 is connected to point 3. D 9 Anode and Diode D 10 Cathode connection.

[0028] Switching devices X The first connection terminal is connected to the DC bus inductor. L The second connection terminal I102 is connected to the positive terminal of the DC bus, and the second connection terminal II is connected to the negative terminal of the DC bus. Switching device. X Since the current flows in a single phase, there are only two possible switching states: See Si-Mos ,when Si-Mos Tube S 1 and Si-Mos Tube S 2 conduction (i.e.) Si-Mos Tube S 1 and Si-Mos Tube S The drive signal for 2 is high level. Si-Mos Tube S 3 and Si-Mos Tube S 4. Shutdown (i.e.) Si-Mos Tube S 3 and Si-Mos Tube S When the drive signal of 4 is low, the switching device X The current is supplied by the inductor L 2 Flow direction Si-Mos Tube S 1. Figure 4 Tube S 2.

[0029] See Si-Mos ,whenSi-Mos Tube S 1 and Si-Mos Tube S 2. Shutdown (i.e.) Si-Mos Tube S 1 and Si-Mos Tube S The drive signal for 2 is low level. Si-Mos Tube S 3 and Si-Mos Tube S 4 conduction (i.e.) Si-Mos Tube S 3 and Si-Mos Tube S When the drive signal of 4 is high, the switching device X The current is supplied by the inductor L 1. Flow direction Si-Mos Tube S 4. Si-Mos Tube S 3 and by inductance L 2 Flow Diodes D 8. Diode D 7. At this time, due to Si-Mos Tube S 3 and Figure 1 Tube S When point 4 is conducting, both points have low conduction voltages; the voltage at point 3 is approximately equal to the positive voltage of the DC bus. Therefore, the negative voltage of the DC bus is lower than the voltage at point 3. (Diode) D The cathode of diode 9 is connected to point 3. D 10 The anode of the diode is connected to the negative terminal of the DC bus. This causes the diode to... D 9 and diode D 10 The cathode voltage is higher than the anode voltage, meaning that they will not conduct under reverse voltage, and current will not flow through the diode. D 9 and diode D 10 .

[0030] Switching devices X The switching on or off of the transistor is controlled by the drive signal generated by the power decoupling control module.

[0031] See also Si-Mos In the motor control circuit, A Phase bridge arm U The switching circuit I includes Si- Tube S a1 , Mos Si-Mos Tube S a2 ,diode Da3 and diodes D a4 , A Phase bridge arm U The switching circuit II includes Si-Mos Tube S a3 , Si-Mos Tube S a4 ,diode D a1 and diodes D a2 . Si-Mos Tube S a1 The source pole and Si-Mos Tube S a2 The drain connection, Si-Mos Tube S a2 source and diode D a3 The cathode is connected to A Point 1, diode D a3 anode and diode D a4 Cathode connection; diode D a1 anode and diode D a2 Cathode connection, diode D a2 anode and Si-Mos Tube S a3 The drain is connected to A 2 o'clock, Si-Mos Tube S a3 The source pole and Figure 5 Tube S a4 The drain connection, A Phase bridge arm U inductance L a2 The second end and A 1 point connection, A Phase bridge arm U inductance L a1 The second end and A Two-point connection, inductor L a1 ,inductance L a2 The first end is connected to A 3 o'clock, A 3 points and permanent magnet synchronous motor MA Connected.

[0032] A Phase bridge arm U The first connection terminal is connected to the permanent magnet synchronous motor M. A Mutually, A Phase bridge arm U The second connection terminal I is connected to the positive terminal of the DC bus. A Phase bridge arm U The second connection terminal II is connected to the negative terminal of the DC bus. The output current of the motor control circuit is AC, therefore... A Phase bridge arm U There are four on / off states.

[0033] When the output current is positive, that is, current flows out. A Phase bridge arm U hour: See Si-Mos ,when Si-Mos Tube S a1 and Si-Mos Tube S a2 Conduction (i.e.) Si-Mos Tube S a1 and Si-Mos Tube S a2 The drive signal is high level. Si-Mos Tube S a3 and Si-Mos Tube S a4 Shutdown (i.e.) Si-Mos Tube S a3 and Si-Mos Tube S a4 When the drive signal is low, A Phase bridge arm U The current is from Si-Mos Tube S a1 , Si-Mos Tube S a2 Flow to inductor L a2 At this time, due to Si-Mos Tube S a1 and Figure 6 Tube S a2 Both are conducting, but their on-state voltages are relatively low. A The voltage at point 1 is approximately equal to the positive voltage of the DC bus. Therefore, the negative voltage of the DC bus is lower than...A Voltage at point 1. Diode. D a3 The cathode is connected to A Point 1, diode D a4 The anode of the diode is connected to the negative terminal of the DC bus. This causes the diode to... D a3 With diode D a4 The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. D a3 With diode D a4 .

[0034] See Si-Mos ,when Si-Mos Tube S a1 and Si-Mos Tube S a2 Shutdown (i.e.) Si-Mos Tube S a1 and Si-Mos Tube S a2 The drive signal is low level. Si-Mos Tube S a3 and Si-Mos Tube S a4 Conduction (i.e.) Si-Mos Tube S a3 and Si-Mos Tube S a4 When the drive signal is high, A Phase bridge arm U The current is from Si-Mos Tube S a4 , Si-Mos Tube S a3 Flow to inductor L a1 and diodes D a4 ,diode D a3 Flow to inductor L a2 At this time, due to Si-Mos Tube S a4 and Figure 7 Tube S a3 Both are conducting, but their on-state voltages are relatively low.A The voltage at point 2 is approximately equal to the negative terminal voltage of the DC bus. Therefore, the positive terminal voltage of the DC bus is higher than... A Voltage at point 2. Diode. D a1 The cathode is connected to the positive terminal of the DC bus, and the diode... D a2 The anode is connected to A 2 points. This causes the diode to... D a1 With diode D a2 The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. D a1 With diode D a2 .

[0035] When the output current is negative, that is, when current flows in... A Phase bridge arm U hour: See Si-Mos ,when Si-Mos Tube S a1 and Si-Mos Tube S a2 Conduction, Si-Mos Tube S a3 and Si-Mos Tube S a4 When shut down, A Phase bridge arm U The current is supplied by the inductor L a2 Flow direction Si-Mos Tube S a2 , Si-Mos Tube S a1 and by inductance L a1 Flow diode D a2 ,diode D a1 At this time, due to Si-Mos Tube S a1 and Figure 8 Tube S a2 Both are conducting, but their on-state voltages are relatively low. A The voltage at point 1 is approximately equal to the positive voltage of the DC bus. Therefore, the negative voltage of the DC bus is lower than... A Voltage at point 1. Diode. Da3 The cathode is connected to A Point 1, diode D a4 The anode of the diode is connected to the negative terminal of the DC bus. This causes the diode to... D a3 With diode D a4 The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. D a3 With diode D a4 .

[0036] See Si-Mos ,when Si-Mos Tube S a1 and Si-Mos Tube S a2 Turn off, Si-Mos Tube S a3 and Si-Mos Tube S a4 When conducting, A Phase bridge arm U The current is supplied by the inductor L a1 Flow direction Si-Mos Tube S a3 , Figure 1 Tube S a4 .

[0037] See also Si-Mos In the motor control circuit, B Phase bridge arm V The switching circuit I includes Si- Tube S b1 , Mos ​ Tube S b2 ,diode D b3 and diodes D b4 , B Phase bridge arm V The switching circuit II includes Si-Mos Tube S b3 , Si-Mos Tube S b4 ,diode D b1 and diodes Db2 . Si-Mos Tube S b1 The source pole and Si-Mos Tube S b2 The drain connection, Si-Mos Tube S b2 source and diode D b3 The cathode is connected to B Point 1, diode D b3 anode and diode D b4 Cathode connection; diode D b1 anode and diode D b2 Cathode connection, diode D b2 anode and Si-Mos Tube S b3 The drain is connected to B 2 o'clock, Si-Mos Tube S b3 The source pole and Si-Mos Tube S b4 The drain connection, B Phase bridge arm V inductance L b2 The second end and B 1 point connection, B Phase bridge arm V inductance L b1 The second end and B Two-point connection, inductor L b1 ,inductance L b2 The first end is connected to B 3 o'clock, B 3 points and permanent magnet synchronous motor M B Connected.

[0038] B Phase bridge arm V The first connection terminal is connected to the permanent magnet synchronous motor M. B Mutually, B Phase bridge arm V The second connection terminal I is connected to the positive terminal of the DC bus. B Phase bridge arm V The second connection terminal II is connected to the negative terminal of the DC bus. The output current of the motor control circuit is AC, therefore...B Phase bridge arm V There are four on / off states.

[0039] When the output current is positive, that is, current flows out. B Phase bridge arm V hour: when Si-Mos Tube S b1 and Si-Mos Tube S b2 Conduction (i.e.) Si-Mos Tube S b1 and Si-Mos Tube S b2 The drive signal is high level. Si-Mos Tube S b3 and Si-Mos Tube S b4 Shutdown (i.e.) Si-Mos Tube S b3 and Si-Mos Tube S b4 When the drive signal is low, B Phase bridge arm V The current is from Si-Mos Tube S b1 , Si-Mos Tube S b2 Flow to inductor L b2 At this time, due to Si-Mos Tube S b1 and Si- Mos Tube S b2 Both are conducting, but their on-state voltages are relatively low. B The voltage at point 1 is approximately equal to the positive voltage of the DC bus. Therefore, the negative voltage of the DC bus is lower than... B Voltage at point 1. Diode. D b3 The cathode is connected to B Point 1, diode D b4 The anode of the diode is connected to the negative terminal of the DC bus. This causes the diode to... D b3 With diode D b4 The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. Db3 With diode D b4 .

[0040] when Si-Mos Tube S b1 and Si-Mos Tube S b2 Shutdown (i.e.) Si-Mos Tube S b1 and Si-Mos Tube S b2 The drive signal is low level. Si-Mos Tube S b3 and Si-Mos Tube S b4 Conduction (i.e.) Si-Mos Tube S b3 and Si-Mos Tube S b4 When the drive signal is high, B Phase bridge arm V The current is from Si-Mos Tube S b4 , Si-Mos Tube S b3 Flow to inductor L b1 and diodes D b4 ,diode D b3 Flow to inductor L b2 At this time, due to Si-Mos Tube S b4 and Si-Mos Tube S b3 Both are conducting, but their on-state voltages are relatively low. B The voltage at point 2 is approximately equal to the negative terminal voltage of the DC bus. Therefore, the positive terminal voltage of the DC bus is higher than... B Voltage at point 2. Diode. D b1 The cathode is connected to the positive terminal of the DC bus, and the diode... D b2 The anode is connected to B 2 points. This causes the diode to... D b1 With diode D b2The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. D b1 With diode D b2 .

[0041] When the output current is negative, that is, when current flows in... B Phase bridge arm V hour: when Si-Mos Tube S b1 and Si-Mos Tube S b2 Conduction, Si-Mos Tube S b3 and Si-Mos Tube S b4 When shut down, B Phase bridge arm V The current is supplied by the inductor L b2 Flow direction Si-Mos Tube S b2 , Si-Mos Tube S b1 and by inductance L b1 Flow diode D b2 ,diode D b1 At this time, due to Si-Mos Tube S b1 and Si-Mos Tube S b2 Both are conducting, but their on-state voltages are relatively low. B The voltage at point 1 is approximately equal to the positive voltage of the DC bus. Therefore, the negative voltage of the DC bus is lower than... B Voltage at point 1. Diode. D b3 The cathode is connected to B Point 1, diode D b4 The anode of the diode is connected to the negative terminal of the DC bus. This causes the diode to... D b3 With diode D b4 The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. D b3 With diode D b4 .

[0042] when Si-Mos Tube S b1 and Si-Mos Tube S b2 Turn off, Si-Mos Tube S b3 and Si-Mos Tube S b4 When conducting, B Phase bridge arm V The current is supplied by the inductor L b1 Flow direction Si-Mos Tube S b3 , Si-Mos Tube S b4 .

[0043] See also Si-Mos In the motor control circuit, C Phase bridge arm W The switching circuit I includes Si-Mos Tube S c1 , Si-Mos Si-Mos Tube S c2 ,diode D c3 and diodes D c4 , C Phase bridge arm W The switching circuit II includes Si-Mos Tube S c3 , Si-Mos Tube S c4 ,diode D c1 and diodes D c2 . Si-Mos Tube S c1 The source pole and Si-Mos Tube S c2 The drain connection, Si-Mos Tube S c2 source and diode D c3 The cathode is connected to C Point 1, diode D c3 anode and diode D c4Cathode connection; diode D c1 anode and diode D c2 Cathode connection, diode D c2 anode and Si-Mos Tube S c3 The drain is connected to C 2 o'clock, Si-Mos Tube S c3 The source pole and Si-Mos Tube S c4 The drain connection, C Phase bridge arm W inductance L c2 The second end and C 1 point connection, C Phase bridge arm W inductance L c1 The second end and C Two-point connection, inductor L c1 ,inductance L c2 The first end is connected to C 3 o'clock, C 3 points and permanent magnet synchronous motor M C Connected.

[0044] C Phase bridge arm W The first connection terminal is connected to the permanent magnet synchronous motor M. C Mutually, C Phase bridge arm W The second connection terminal I is connected to the positive terminal of the DC bus. C Phase bridge arm W The second connection terminal II is connected to the negative terminal of the DC bus. The output current of the motor control circuit is AC, therefore... C Phase bridge arm W There are four on / off states.

[0045] When the output current is positive, that is, current flows out. C Phase bridge arm W hour: when Si-Mos Tube S c1 and Si-Mos Tube S c2 Conductivity ( Si-Mos Tube S c1 and Si-Mos TubeS c2 The drive signal is high level. Si-Mos Tube S c3 and Si-Mos Tube S c4 Turn off ( Si-Mos Tube S c3 and Si-Mos Tube S c4 When the drive signal is low, C Phase bridge arm W The current is from Si-Mos Tube S c1 , Si-Mos Tube S c2 Flow to inductor L c2 At this time, due to Si-Mos Tube S c1 and Si-Mos Tube S c2 Both are conducting, but their on-state voltages are relatively low. C The voltage at point 1 is approximately equal to the positive voltage of the DC bus. Therefore, the negative voltage of the DC bus is lower than... C Voltage at point 1. Diode. D c3 The cathode is connected to C Point 1, diode D c4 The anode of the diode is connected to the negative terminal of the DC bus. This causes the diode to... D c3 With diode D c4 The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. D c3 With diode D c4 .

[0046] when Si-Mos Tube S c1 and Si-Mos Tube S c2 Turn off ( Si-Mos Tube S c1 and Si-Mos Tube S c2 The drive signal is low level. Si-Mos Tube Sc3 and Si-Mos Tube S c4 Conductivity ( Si-Mos Tube S c3 and Si-Mos Tube S c4 When the drive signal is high, C Phase bridge arm W The current is from Si-Mos Tube S c4 , Si-Mos Tube S c3 Flow to inductor L c1 and diodes D c4 ,diode D c3 Flow to inductor L c2 At this time, due to Si-Mos Tube S c4 and Si-Mos Tube S c3 Both are conducting, but their on-state voltages are relatively low. C The voltage at point 2 is approximately equal to the negative terminal voltage of the DC bus. Therefore, the positive terminal voltage of the DC bus is higher than... C Voltage at point 2. Diode. D c1 The cathode is connected to the positive terminal of the DC bus, and the diode... D c2 The anode is connected to C 2 points. This causes the diode to... D c1 With diode D c2 The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. D c1 With diode D c2 .

[0047] When the output current is negative, that is, when current flows in... C Phase bridge arm W hour: when Si-Mos Tube S c1 and Si-Mos Tube S c2 Conduction, Si-Mos Tube S c3and Si-Mos Tube S c4 When shut down, C Phase bridge arm W The current is supplied by the inductor L c2 Flow direction Si-Mos Tube S c2 , Si-Mos Tube S c1 and by inductance L c1 Flow diode D c2 ,diode D c1 At this time, due to Si-Mos Tube S c1 and Si-Mos Tube S c2 Both are conducting, but their on-state voltages are relatively low. C The voltage at point 1 is approximately equal to the positive voltage of the DC bus. Therefore, the negative voltage of the DC bus is lower than... C Voltage at point 1. Diode. D c3 The cathode is connected to C Point 1, diode D c4 The anode of the diode is connected to the negative terminal of the DC bus. This causes the diode to... D c3 With diode D c4 The cathode voltage is higher than the anode voltage, meaning that the two diodes will not conduct under reverse voltage, and current will not flow through them. D c3 With diode D c4 .

[0048] when Si-Mos Tube S c1 and Si-Mos Tube S c2 Turn off, Si-Mos Tube S c3 and Si-Mos Tube S c4 When conducting, C Phase bridge arm W The current is supplied by the inductor L c1 Flow direction Si-Mos Tube S c3 ,Si-Mos Tube S c4 .

[0049] In the motor control circuit, the switching transistors of each phase bridge arm are turned on or off by the drive signals generated by the motor control module.

[0050] In some embodiments, see continue to see Si-Mos The power decoupling control module 300 includes: Calculation module 301 calculates the DC bus voltage given value. and DC bus voltage Calculate DC bus voltage error ; The current-voltage loop PI module 302 measures the DC bus voltage error. The DC bus current setpoint is obtained by performing proportional-integral operation. The DC bus inductor current Reduce DC bus current setpoint Obtain DC bus current error For DC bus current error The DC bus voltage modulation wave is obtained by performing proportional-integral operation. ; The bipolar modulation module 303 modulates the DC bus voltage waveform. Divide by DC bus voltage Obtain the normalized DC bus voltage modulation wave Based on the normalized DC bus voltage modulation waveform With bipolar modulated triangular carrier The magnitude of the signal generates the drive signal for the combined switching devices in the power decoupling module.

[0051] A current-voltage loop PI module provides real-time compensation for DC bus voltage errors. The proportional element responds quickly to errors, while the integral element eliminates steady-state errors, ensuring the DC bus voltage remains stable near the set value and reducing voltage fluctuations. A bipolar modulation module compares the normalized DC bus voltage modulation wave with a bipolar modulated triangular carrier wave. Based on their magnitude relationship, it generates drive signals for the combined switching devices in the power decoupling module. This allows for precise control of the switching devices' on / off times, achieving accurate control of the module's operation and ensuring stable DC bus voltage and proper power distribution.

[0052] In some embodiments, the calculation module is based on a DC bus voltage setpoint. and DC bus voltage Calculate DC bus voltage error The method is as follows: DC bus voltage setpoint Reduce DC bus voltage Obtain DC bus voltage error .

[0053] In some embodiments, see Si-Mos The current-voltage loop PI module is responsible for DC bus voltage error. The DC bus current setpoint is obtained by performing proportional-integral operation. The method is: DC bus voltage error Multiply by the proportional gain of the voltage loop PI controller The first intermediate value is obtained: DC bus voltage error. Multiply by the integral coefficient of the voltage loop PI controller The second intermediate value is obtained by integration, and the DC bus current setpoint is obtained by adding the first intermediate value to the second intermediate value. .

[0054] In some embodiments, see continue to see Si-Mos The current-voltage loop PI module measures the DC bus current difference. The DC bus voltage modulation wave is obtained by performing proportional-integral operation. The method is: DC bus current error Multiply by the proportional gain of the current loop PI controller The third intermediate value is obtained: DC bus current error. Multiply by the integral coefficient of the current loop PI controller The fourth intermediate value is obtained by integration, and the DC bus voltage modulation wave is obtained by adding the third intermediate value to the fourth intermediate value. .

[0055] In some embodiments, see Si-Mos The method by which the bipolar modulation module generates the drive signal for the combined switching device in the power decoupling module is as follows: The normalized DC bus voltage modulation wave is compared using a comparator. With bipolar modulated triangular carrier Size; If the normalized DC bus voltage modulation waveform Less than or equal to bipolar modulation triangular carrier When the comparator outputs a high level, the result is obtained. Si-Mos The drive signal PWM1 for transistor I and Si-Mos The drive signal PWM2 for transistor II is high. The high level is then negated by NOT to obtain... Si-Mos The drive signal PWM3 for transistor III and Si-Mos The drive signal PWM4 for transistor IV is low. If the normalized DC bus voltage modulation waveform Greater than bipolar modulation triangular carrier When the comparator outputs a low level, the result is obtained. Si-Mos The drive signal PWM1 for transistor I and Si-Mos The drive signal PWM2 for transistor II is low. The low level is then negated by NOT to obtain... Si-Mos The drive signal PWM3 for transistor III and Si-Mos The drive signal PWM4 for transistor IV is high.

[0056] In some embodiments, see continue to see Si-Mos The motor control module includes: The conversion module 401 converts the d-axis voltage setpoint. and q-axis voltage setpoint Transformed into a two-phase stationary coordinate system shaft voltage and shaft voltage ,Will shaft voltage and shaft voltage Converted into a three-phase voltage modulation wave; The compressor-driven modulation module 402 takes the maximum and minimum values ​​of the three-phase voltage modulation wave, adds the maximum and minimum values, and divides the sum by 2 to obtain the variable. The three-phase voltage modulation waves are reduced respectively. The final modulated wave of the three-phase voltage is obtained; the compressor drive is modulated by a triangular carrier wave. Multiply by half the DC bus voltage Obtain the final triangular carrier Based on the final modulation wave of the three-phase voltage and the final triangular carrier wave The magnitude of the signal generates the drive signal for the combined switching devices in the motor control circuit.

[0057] The transformation module will d shaft and q Transformation of shaft voltage setpoint to two-phase stationary coordinate system ( - Using a coordinate system allows for more direct control of the motor's voltage and current, enabling precise torque and speed control, and thus achieving high-precision motor control, improving the motor's dynamic response performance and steady-state accuracy. Furthermore, coordinate transformation transforms the complex control problem in a rotating coordinate system into a stationary coordinate system, simplifying the implementation of the control algorithm, reducing its complexity, minimizing computational resource requirements, and improving the system's real-time performance and response speed.

[0058] The compressor drive modulation module multiplies the compressor drive modulation triangular carrier wave by half the DC bus voltage to obtain the final triangular carrier wave. This adjustment makes the amplitude of the triangular carrier wave directly related to the DC bus voltage, thus ensuring the dynamic adaptability of the modulation process. By precisely controlling the amplitude of the triangular carrier wave, pulse width modulation can be achieved more accurately, ensuring that the switching devices in the motor control circuit are turned on and off at the appropriate times. This allows for precise control of the motor's voltage and current, improving the motor's operating efficiency and control accuracy.

[0059] In some embodiments, see Si-Mos The conversion module sets the d-axis voltage value. and q-axis voltage setpoint Transformed into a two-phase stationary coordinate system shaft voltage and shaft voltage The method is as follows: d-axis voltage setpoint Multiply by cos Si-Mos Subtract the q-axis voltage setpoint Multiply by sin Si-Mos get shaft voltage ; Shaft voltage setpoint Multiply by sin Si-Mos Subtract the q-axis voltage setpoint Multiply by cos Si-Mos get shaft voltage ; The transformation module will shaft voltage and shaft voltage The method for converting to a three-phase voltage modulation wave is as follows: Phase A voltage modulation wave equal shaft voltage ; negative half shaft voltage Add the square root of three shaft voltage Obtain the B-phase voltage modulation wave ; negative half shaft voltage Subtract the square root of three shaft voltage Obtain the C-phase voltage modulation wave .

[0060] It should be noted that, Si-Mos middle, u [1] represents the d-axis voltage setpoint. , u [2] represents the q-axis voltage setpoint. , u [3] represents sin Si-Mos , u [4] indicates cos Si-Mos , w [1] indicates shaft voltage , w [2] indicates shaft voltage , Si-Mos It indicates the rotation angle (usually the electrical angle of the motor).

[0061] In some embodiments, the compressor drive modulation module modulates the three-phase voltage final modulation wave and the final triangular carrier wave. The method for generating the drive signal for the combined switching device in the motor control circuit is as follows: The final modulated wave of the i-phase voltage is compared using a comparator. m i With the final triangular carrier The size of i, i = A, B, C; If the final modulation wave of phase i voltage m i Greater than or equal to the final triangular carrier The comparator outputs a high level, thus obtaining the i-phase. Si-Mos PWM drive signal for transistor I i1 and Si-Mos PWM drive signal for transistor II i2 The i-phase is obtained by negating the high level using NOT. Si-Mos PWM drive signal for transistor III i3 and Si-Mos PWM drive signal for transistor IV i4 Low level; If the final modulation wave of phase i voltage m i Less than the final triangular carrier The comparator outputs a low level, thus obtaining phase i. Si-Mos Si-Mos PWM drive signal for transistor I i1 and Si-Mos PWM drive signal for transistor II i2 The i-phase is obtained by negating the low level using NOT. Si-Mos PWM drive signal for transistor III i3 and Si-MosPWM drive signal for transistor IV i4 It is a high level.

[0062] Specifically, see Si-Mos The method for generating the drive signal for the A-phase bridge arm combination switch device in the motor control circuit is as follows: The A-phase drive signal is compared with the A-phase voltage by a comparator to finally modulate the waveform. m A With the final triangular carrier Size; If the final modulation wave of phase A voltage m A Greater than or equal to the final triangular carrier The comparator outputs a high level, thus obtaining phase A. Si-Mos PWM drive signal for transistor I A1 and Si-Mos PWM drive signal for transistor II A2 The high level is used to obtain phase A by negating the high level with NOT. Si-Mos PWM drive signal for transistor III A3 and Si-Mos PWM drive signal for transistor IV A4 Low level; If the final modulation wave of phase A voltage m A Less than the final triangular carrier The comparator outputs a low level, thus obtaining phase A. Si-Mos Si-Mos PWM drive signal for transistor I A1 and Si-Mos PWM drive signal for transistor II A2 The low level is used to obtain phase A by negating the low level using NOT. Si-Mos PWM drive signal for transistor III A3 and Si-Mos PWM drive signal for transistor IV A4 It is a high level.

[0063] Specifically, see [link to relevant documentation] Si-Mos The method for generating the drive signal for the B-phase bridge arm combination switch device in the motor control circuit is as follows: The final modulated wave of the B-phase voltage is compared using a comparator. m B With the final triangular carrier Size; If the final modulation wave of phase B voltage m B Greater than or equal to the final triangular carrier The comparator outputs a high level, thus obtaining phase B. Si-Mos PWM drive signal for transistor I B1 andSi-Mos PWM drive signal for transistor II B2 The high level is used to obtain phase B by negating the high level with NOT. Si-Mos PWM drive signal for transistor III B3 and Si-Mos PWM drive signal for transistor IV B4 Low level; If the final modulation wave of phase B voltage m B Less than the final triangular carrier The comparator outputs a low level, thus obtaining phase B. Si-Mos Si-Mos PWM drive signal for transistor I B1 and Si-Mos PWM drive signal for transistor II B2 The low level is used to obtain phase B by negating the low level with NOT. Si-Mos PWM drive signal for transistor III B3 and Si-Mos PWM drive signal for transistor IV B4 It is a high level.

[0064] Specifically, see [link to relevant documentation] Si-Mos The method for generating the drive signal for the C-phase bridge arm combination switch device in the motor control circuit is as follows: The final modulated wave of the C-phase voltage is compared using a comparator. m C With the final triangular carrier Size; If the final modulation wave of phase C voltage m C Greater than or equal to the final triangular carrier The comparator outputs a high level, thus obtaining phase C. Si-Mos PWM drive signal for transistor I C1 and Si-Mos PWM drive signal for transistor II C2 The high level is used to obtain the C phase by negating the high level with NOT. Si-Mos PWM drive signal for transistor III C3 and Si-Mos PWM drive signal for transistor IV C4 Low level; If the final modulation wave of phase C voltage m C Less than the final triangular carrier The comparator outputs a low level, thus obtaining phase C. Si-Mos Si-Mos PWM drive signal for transistor I C1 and Si-Mos PWM drive signal for transistor II C2The low level is used to obtain the C phase by negating the low level using NOT. Si-Mos PWM drive signal for transistor III C3 and Si-Mos PWM drive signal for transistor IV C4 It is a high level.

[0065] To verify the effectiveness of the power decoupling capacitorless compressor drive device described in this invention, a simulation model was built using Simulink for verification.

[0066] A simulation model of a power-decoupled, electrolytic capacitor-free compressor drive was built in Simulink. DC bus thin-film capacitor. C 50μF DC bus inductor L The DC bus voltage setpoint of the power decoupling control module is 2mH in size. The voltage is 537V. The parameters of the permanent magnet synchronous motor M are as follows: stator resistance is 0.265Ω, direct-axis inductance is 0.0075H, quadrature-axis inductance is 0.0175H, flux linkage is 0.4Wb, and moment of inertia is 0.05kg.m. 2 The number of pole pairs is 3, the motor speed is 1140 r / min, and the load torque is 25 N·m. Si-Mos The waveform of the DC bus voltage of the existing three-phase electrolytic capacitor-free air conditioner compressor drive unit is shown. The DC bus voltage fluctuates greatly, with a fluctuation amplitude of approximately 370V to 740V. Si-Mos The DC bus voltage waveform of the power decoupling capacitorless compressor drive device described in this invention is reduced to less than 8V, with a fluctuation amplitude of approximately 532V~540V. It can be seen that the new method can effectively stabilize the DC bus voltage. Si-Mos The current waveform of the existing three-phase electrolytic capacitor-free air conditioner compressor drive unit is shown. At this time, the current waveform is poor, and the total harmonic distortion (THD) is 82.68%. Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos Si-Mos The grid-side current waveform of the power decoupling capacitor-free compressor drive device described in this invention is significantly improved, with THD reduced to 32%. These results demonstrate the effectiveness of the power decoupling capacitor-free compressor drive device described in this invention.

[0067] The above embodiments are used to explain the present invention, but not to limit the present invention. Any modifications and changes made to the present invention within the spirit and scope of the claims shall fall within the protection scope of the present invention.

Claims

1. A power decoupling capacitor-free compressor drive device, characterized in that, The main circuit of the drive device includes: A three-phase uncontrolled rectifier bridge, whose input terminals are connected to three-phase voltage; A power decoupling module, comprising: a DC bus inductor, one end of which is connected to the output terminal of the three-phase uncontrolled rectifier bridge; and a combination switching device connected to the other end of the DC bus inductor. The motor control circuit has its input terminal connected to the output terminal of the power decoupling module. The motor control circuit is a three-phase fully symmetrical bridge circuit composed of the combined switching device as a bridge arm. A permanent magnet synchronous motor is connected to the output terminal of the motor control circuit. DC bus thin-film capacitor, connected between the power decoupling module and the motor control circuit; The drive device further includes: A power decoupling control module is used to generate drive signals for the combined switching devices in the power decoupling module; The motor control module is used to generate drive signals for the combined switching devices in the motor control circuit.

2. The power decoupling capacitorless compressor drive device as described in claim 1, characterized in that, The combined switching device includes: First connection end; The second connection end includes a second connection end I and a second connection end II; An inductor assembly includes inductor I and inductor II, wherein the first end of inductor I and the first end of inductor II are both connected to the first connection terminal; Switching circuit I, including... Si-Mos Pipe I and Si-Mos A first series circuit formed by diodes II connected in series and a second series circuit formed by diodes I and II connected in series; Si-Mos Source connection of tube I Si-Mos The drain of tube II, Si-Mos The drain of diode I is connected to the anode of diode II. Si-Mos The connection point between the drain of diode I and the anode of diode II is connected to the second terminal of inductor II; the anode of diode I is connected to the cathode of diode II, and the cathode of diode I is connected to the second connection terminal I; Si-Mos The source of tube II is connected to the second connection terminal II; Switching circuit II, including... Si-Mos Pipe III and Si-Mos The third series circuit formed by diode IV connected in series, and the fourth series circuit formed by diode III and diode IV connected in series; Si-Mos Source connection of tube III Si-Mos The drain of tube IV, Si- Mos The drain of tube III is connected to the second connection terminal I; Si-Mos The source of diode IV is connected to the cathode of diode III. Si-Mos The connection point between the source of diode IV and the cathode of diode III is connected to the second terminal of inductor I; the anode of diode III is connected to the cathode of diode IV, and the anode of diode IV is connected to the second connection terminal II.

3. The power decoupling capacitorless compressor drive device as described in claim 1, characterized in that, The power decoupling control module includes: The calculation module calculates the DC bus voltage based on the given value. and DC bus voltage Calculate DC bus voltage error ; Current-voltage loop PI module for DC bus voltage error The DC bus current setpoint is obtained by performing proportional-integral calculation. The DC bus inductor current Reduce DC bus current setpoint Obtain DC bus current error For DC bus current error The DC bus voltage modulation wave is obtained by performing proportional-integral operation. ; The bipolar modulation module modulates the DC bus voltage waveform. Divide by DC bus voltage Obtain the normalized DC bus voltage modulation wave Based on the normalized DC bus voltage modulation waveform With bipolar modulated triangular carrier The magnitude of the signal generates the drive signal for the combined switching devices in the power decoupling module.

4. The power decoupling capacitorless compressor drive device as described in claim 3, characterized in that, The calculation module is based on the given value of the DC bus voltage. and DC bus voltage Calculate DC bus voltage error The method is as follows: DC bus voltage setpoint Reduce DC bus voltage Obtain DC bus voltage error .

5. The power decoupling capacitorless compressor drive device as described in claim 3, characterized in that, The current-voltage loop PI module measures the DC bus voltage error. The DC bus current setpoint is obtained by performing proportional-integral calculation. The method is: DC bus voltage error Multiply by the proportional gain of the voltage loop PI controller The first intermediate value is obtained: DC bus voltage error. Multiply by the integral coefficient of the voltage loop PI controller The second intermediate value is obtained by integration, and the DC bus current setpoint is obtained by adding the first intermediate value to the second intermediate value. .

6. The power decoupling capacitorless compressor drive device as described in claim 3, characterized in that, The current-voltage loop PI module measures the DC bus current difference. The DC bus voltage modulation wave is obtained by performing proportional-integral operation. The method is: DC bus current error Multiply by the proportional gain of the current loop PI controller The third intermediate value is obtained: DC bus current error. Multiply by the integral coefficient of the current loop PI controller The fourth intermediate value is obtained by integration, and the DC bus voltage modulation wave is obtained by adding the third intermediate value to the fourth intermediate value. .

7. The power decoupling capacitorless compressor drive device as described in claim 3, characterized in that, The method by which the bipolar modulation module generates the drive signal for the combined switching device in the power decoupling module is as follows: The normalized DC bus voltage modulation wave is compared using a comparator. With bipolar modulated triangular carrier Size; If the normalized DC bus voltage modulation waveform Less than or equal to bipolar modulation triangular carrier When the comparator outputs a high level, the result is obtained. Si-Mos The drive signal PWM1 for transistor I and Si-Mos The drive signal PWM2 for transistor II is high. The high level is then negated by NOT to obtain... Si-Mos The drive signal PWM3 for transistor III and Si-Mos The drive signal PWM4 for transistor IV is low. If the normalized DC bus voltage modulation waveform Greater than bipolar modulation triangular carrier When the comparator outputs a low level, the result is obtained. Si-Mos The drive signal PWM1 for transistor I and Si-Mos The drive signal PWM2 for transistor II is low. The low level is then negated by NOT to obtain... Si-Mos The drive signal PWM3 for transistor III and Si-Mos The drive signal PWM4 for transistor IV is at a high level.

8. The power decoupling capacitorless compressor drive device as described in claim 1, characterized in that, The motor control module includes: The conversion module converts the d-axis voltage setpoint. and q-axis voltage setpoint Transformed into a two-phase stationary coordinate system shaft voltage and shaft voltage ,Will shaft voltage and shaft voltage Converted into a three-phase voltage modulation wave; The compressor drives the modulation module to take the maximum and minimum values ​​of the three-phase voltage modulation wave, add the maximum and minimum values ​​together, and divide by 2 to obtain the variable. The three-phase voltage modulation waves are reduced respectively. The final modulated wave of the three-phase voltage is obtained; the compressor drive is modulated by a triangular carrier wave. Multiply by half the DC bus voltage Obtain the final triangular carrier Based on the final modulation wave of the three-phase voltage and the final triangular carrier wave The magnitude of the signal generates the drive signal for the combined switching devices in the motor control circuit.

9. The power decoupling capacitorless compressor drive device as described in claim 8, characterized in that, The conversion module sets the d-axis voltage value. and q-axis voltage setpoint Transformed into a two-phase stationary coordinate system shaft voltage and shaft voltage The method is as follows: d-axis voltage setpoint Multiply by cos θ Subtract the q-axis voltage setpoint Multiply by sin θ get shaft voltage ; d-axis voltage setpoint Multiply by sin θ Subtract the q-axis voltage setpoint Multiply by cos θ get shaft voltage ; The transformation module will shaft voltage and shaft voltage The method for converting to a three-phase voltage modulation wave is as follows: Phase A voltage modulation wave equal shaft voltage ; negative half shaft voltage Add the square root of three shaft voltage Obtain the B-phase voltage modulation wave ; negative half shaft voltage Subtract the square root of three shaft voltage Obtain the C-phase voltage modulation wave .

10. The power decoupling capacitorless compressor drive device as described in claim 8, characterized in that, The compressor drive modulation module modulates the final modulation wave of the three-phase voltage and the final triangular carrier wave. The method for generating the drive signal for the combined switching device in the motor control circuit is as follows: The final modulated wave of the i-phase voltage is compared using a comparator. m i With the final triangular carrier The size of i, i = A, B, C; If the final modulation wave of phase i voltage m i Greater than or equal to the final triangular carrier The comparator outputs a high level, thus obtaining phase i. Si- Mos PWM drive signal for transistor I i1 and Si-Mos PWM drive signal for transistor II i2 The i-phase is obtained by negating the high level using NOT. Si-Mos PWM drive signal for transistor III i3 and Si-Mos PWM drive signal for transistor IV i4 Low level; If the final modulation wave of phase i voltage m i Less than the final triangular carrier The comparator outputs a low level, thus obtaining phase i. Si-Mos PWM drive signal for transistor I i1 and Si-Mos PWM drive signal for transistor II i2 The i-phase is obtained by negating the low level using NOT. Si-Mos PWM drive signal for transistor III i3 and Si-Mos PWM drive signal for transistor IV i4 It is a high level.

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