Magnetic integrated cross-inductance voltage stabilizer circuit, control method and equipment

Abstract

The invention discloses a magnetic integrated cross-inductance voltage stabilizer circuit, a control method and equipment, the magnetic integrated cross-inductance voltage stabilizer circuit comprises a plurality of half-bridge circuits and a plurality of TLVR inductors, the plurality of half-bridge circuits comprise a first half-bridge circuit to an Mth half-bridge circuit which are arranged in sequence, the first half-bridge circuit to the Mth half-bridge circuit are divided into at least one circuit group, and the first half-bridge circuit to the Mth half-bridge circuit are connected with the TLVR inductors. Each circuit group comprises at least two half-bridge circuits which are adjacent in sequence, the TLVR inductors connected with the half-bridge circuits in any circuit group share a magnetic core so as to be integrated into a magnetic integrated TLVR inductor, and the connection mode of the half-bridge circuits and the TLVR inductors and the winding direction of a primary winding and a secondary winding in any magnetic integrated TLVR inductor are different. The magnetic flux in the common magnetic core area between the adjacent TLVR inductors in the magnetic integrated TLVR inductor can be partially or completely counteracted, the size of the common magnetic core area is reduced, the overall size of the magnetic integrated TLVR inductor is reduced, and the loss of the magnetic integrated TLVR inductor is reduced.

Description

Technical Field

[0001] This application relates to the field of chip power supply technology, and in particular to a magnetically integrated transinductance voltage regulator circuit, control method and device. Background Technology

[0002] With the development of technologies such as artificial intelligence and machine learning, the computing power requirements of data center computing chips (such as application-specific integrated circuits (ASICs), central processing units (CPUs), and graphics processing units (GPUs)) are increasing rapidly. Such applications require extremely high load currents (e.g., greater than 1000A) and extremely fast load dynamics (e.g., greater than 2000A / μs), placing extremely high demands on the dynamic response performance of switching power supplies.

[0003] Trans-Inductor Voltage Regulator (TLVR) circuits are a topology used in switching power supplies, and typically use a transformer-like TLVR inductor as the output inductor. Currently, one type of TLVR circuit uses a discrete TLVR inductor, resulting in a large overall TLVR inductor size, which is detrimental to miniaturizing and modularizing the switching power supply for placement near computing chips. Another type of TLVR circuit integrates the TLVR inductor, but this integration achieves negative coupling, weakening the dynamic performance of the TLVR circuit and making it prone to core saturation due to current imbalance, posing a risk of core burnout. However, to reduce the risk of core saturation, the core width needs to be increased, resulting in a larger core size and consequently a larger integrated TLVR inductor size, which also hinders the miniaturization and modularization of the switching power supply for placement near computing chips. Summary of the Invention

[0004] This application provides a magnetically integrated transinductance regulator circuit, control method, and device to reduce the overall size of the TLVR inductor in the TLVR circuit while ensuring a high dynamic response. This facilitates the miniaturization and modularization of the switching power supply for placement closer to the computing chip.

[0005] In a first aspect, embodiments of this application provide a magnetically integrated TLVR circuit, which includes multiple half-bridge circuits and multiple TLVR inductors. The first terminal of any half-bridge circuit is connected to the power input terminal, and the second terminal of any half-bridge circuit is connected to the ground terminal. Furthermore, each of the multiple TLVR inductors corresponds one-to-one with a half-bridge circuit; the switching node of any half-bridge circuit is connected to the first terminal of the primary winding of the corresponding TLVR inductor, and the second terminal of the primary winding of any TLVR inductor is connected to the power output terminal. With this configuration, the secondary windings of the multiple TLVR inductors and the compensation loop inductor are connected in series to form a series circuit, and this series circuit is connected to the ground terminal. Therefore, by designing a suitable inductance value for the compensation loop inductor, high steady-state inductance and low transient inductance can be achieved, resulting in low current ripple, high efficiency, and high transient response speed.

[0006] Furthermore, the multiple half-bridge circuits include sequentially arranged first to Mth half-bridge circuits, which are divided into at least one circuit group. Each circuit group includes at least two sequentially adjacent half-bridge circuits. The TLVR inductors connected to each half-bridge circuit in any circuit group share a common magnetic core to form a single magnetically integrated TLVR inductor, which can reduce the overall size of the TLVR inductor.

[0007] Furthermore, in any magnetically integrated TLVR inductor, the mutual inductance coupling coefficient of each primary winding is greater than zero. This means that when current flows into the first end of each primary winding, the magnetic field generated by each primary winding is in the same direction, thus forming a weak positive coupling between different primary windings in any magnetically integrated TLVR inductor, which can reduce interference between different primary windings in any magnetically integrated TLVR inductor. Moreover, the winding direction of each primary winding from the first end to the second end is the same as the winding direction of each secondary winding from the first end to the second end, enabling strong positive coupling between the primary and secondary windings of any TLVR inductor. Based on the series coupling of the secondary windings of the TLVR inductor, the output current slope is improved by utilizing the dynamic linkage of the secondary windings, reducing the equivalent output inductance. Additionally, changes in load current can have a faster impact on any half-bridge circuit, achieving a faster transient response.

[0008] Furthermore, in this embodiment, based on the connection method of the half-bridge circuit and the TLVR inductor, and the fact that the mutual inductance coupling coefficient of each primary winding in any magnetically integrated TLVR inductor is greater than zero, and the winding directions of the primary and secondary windings, when the magnetically integrated TLVR circuit is working, the magnetic flux in the common core region between adjacent TLVR inductors can be partially or completely canceled out, thereby reducing the volume of the common core region, and further reducing the volume of the magnetic core of the magnetically integrated TLVR inductor. This is beneficial for reducing the overall volume of the magnetically integrated TLVR inductor and reducing its losses.

[0009] In some embodiments, in any TLVR inductor, the secondary winding is wound on the magnetic core, and the primary winding is wound on the secondary winding, with an insulating layer between the primary and secondary windings to prevent short circuits, forming a nested structure. This further reduces the space occupied by each TLVR inductor. Furthermore, the nested structures in any magnetically integrated TLVR inductor can be arranged sequentially at intervals along the extension direction of the magnetic core. With this configuration, combined with the aforementioned half-bridge circuit and TLVR inductor connection method, after current is input to the primary and secondary windings, the magnetic flux in the common magnetic core between adjacent nested structures can be partially or completely canceled out. Therefore, the spacing between adjacent nested structures can be set smaller, further reducing the size of the magnetically integrated TLVR inductor.

[0010] For example, the insulating layer can be configured as a gas gap, an insulating material film, etc.

[0011] In some embodiments, the primary winding has a sheet-like first U-shaped structure, and the secondary winding has a sheet-like second U-shaped structure. The second U-shaped structure is disposed within the accommodating cavity of the first U-shaped structure, and the opening directions of the second U-shaped structure and the first U-shaped structure are the same. This configuration, where the first and second U-shaped structures are only tightly bonded by an insulating layer and do not contain any magnetically conductive material, allows for close proximity yet electrical isolation between the two U-shaped structures, resulting in strong coupling between them. Furthermore, the sheet-like first and second U-shaped structures provide good connection stability, improving the connection stability of the inductor.

[0012] To improve the reliability and stability of the connection between the first U-shaped structure and the second U-shaped structure, pins can be extended from both ends of the openings of the first and second U-shaped structures for connection via the pins. In some embodiments, the primary winding also has a lamellar first pin and a lamellar second pin, the first pin being connected to one end of the first U-shaped structure and extending outward, and the second pin being connected to the other end of the first U-shaped structure and extending outward. Furthermore, the secondary winding also has a lamellar third pin and a lamellar fourth pin, the third pin being connected to one end of the second U-shaped structure and extending inward, and the fourth pin being connected to the other end of the second U-shaped structure and extending inward. In any TLVR inductor, the first pin and the third pin are spaced apart to form a first end, and the second pin and the fourth pin are spaced apart to form a second end.

[0013] In some embodiments, the first U-shaped structure, the first pin, and the second pin in any primary winding can be configured as an integrally formed structure of the same material, and the second U-shaped structure, the third pin, and the fourth pin in any secondary winding can also be configured as an integrally formed structure of the same material.

[0014] In some embodiments, the connection between the first and second pins and the first U-shaped structure can be configured as a bent shape to reduce stress at the connection and improve stability. Similarly, the connection between the third and fourth pins and the second U-shaped structure can also be configured as a bent shape to reduce stress at the connection and improve stability.

[0015] In some embodiments, the primary and secondary windings of any magnetically integrated TLVR inductor can be embedded in the magnetic core to improve their tightness of connection, and the magnetic core is used to protect the primary and secondary windings.

[0016] In some embodiments, a one-piece die-casting process can be used to die-cast the TLVR inductor in each magnetically integrated TLVR inductor, thereby enabling each magnetically integrated TLVR inductor to be configured as a single-piece structure. Since the one-piece die-casting process utilizes a mold for direct molding, it avoids errors and deformation problems that may exist in traditional processing, thus improving the accuracy and quality of the magnetically integrated TLVR inductor. Furthermore, the one-piece die-casting process is highly automated, significantly improving production efficiency and reducing labor and material costs. In addition, since the one-piece die-casting process eliminates the need for multiple steps, it also saves manufacturing time.

[0017] Heat is generated when current is transmitted through the primary and secondary windings. If the heat cannot be dissipated in time, it will affect the overall performance of the device. In some embodiments, in order to improve the heat dissipation effect of the magnetically integrated TLVR inductor, the upper surface of the side of each first U-shaped structure facing away from its opening in at least one magnetically integrated TLVR inductor can be exposed outside the magnetic core.

[0018] To further improve the heat dissipation of the magnetically integrated TLVR inductor, in some embodiments, the magnetic core of at least one magnetically integrated TLVR inductor may be arranged to protrude from the side opposite to the opening of each first U-shaped structure.

[0019] In some embodiments, in a magnetically integrated TLVR circuit, the leakage inductance of at least one TLVR inductor can be designed to integrate the compensation loop inductor into the TLVR inductor through leakage inductance, thereby eliminating the physical components of the compensation loop inductor and further reducing the size of the magnetic components in the magnetically integrated TLVR circuit.

[0020] Furthermore, in practical applications, the controller can control some or all of the half-bridge circuits to simultaneously output the bus voltage at the power input terminal, thereby reducing control complexity. However, during transient processes, multiple half-bridge circuits simultaneously outputting the bus voltage at the power input terminal in a magnetically integrated TLVR circuit can lead to voltage accumulation in the series-connected secondary windings, resulting in insulation withstand voltage risks. In this embodiment, by integrating a leakage inductance into the TLVR inductor, since the leakage inductance can generate a negative voltage, the negative voltage generated by the integrated leakage inductance can also offset the voltage of the primary winding, thereby reducing the maximum voltage of the series circuit of the secondary winding, thus reducing voltage accumulation in the series circuit of the secondary winding, which is beneficial for insulation design. In addition, it can also reduce control complexity.

[0021] In some embodiments, an adjustment structure can be integrated into each TLVR inductor to adjust the leakage inductance of the TLVR inductor, thereby making the compensation circuit inductance the leakage inductance of the TLVR inductor with the integrated adjustment structure.

[0022] In some embodiments, adjustment structures may be filled between the bending regions between the first pin and the first U-shaped structure and between the third pin and the second U-shaped structure; or, adjustment structures may be filled between the bending regions between the second pin and the first U-shaped structure and between the fourth pin and the second U-shaped structure. This arrangement ensures that the volume of the magnetic core or the area of ​​the windings is not sacrificed by filling these gaps with adjustment structures.

[0023] In some embodiments, the adjustment structure may include: a magnetic core material and an insulating material layer disposed between the magnetic core material and the primary winding and the secondary winding. This configuration allows the magnetic core material covered by the insulating material layer to fill the aforementioned gaps, reducing the difficulty of material selection and facilitating the formation of a single-piece structure for the magnetically integrated TLVR inductor.

[0024] In some embodiments, in a magnetically integrated TLVR circuit, the compensation loop inductor can also be implemented using a physical inductor element, thereby allowing the compensation loop inductor and the secondary winding to be set independently of each other and connected by wires.

[0025] In some embodiments, each half-bridge circuit is also connected to a controller. During operation, the controller outputs a pulse width modulation (PWM) signal to each half-bridge circuit to control the operation of each half-bridge circuit. Combined with the TLVR inductor, buck conversion can be achieved.

[0026] For example, each half-bridge circuit includes a first switch and a second switch connected in series between a power input terminal and a ground terminal. The control terminals of the first and second switches are connected to a controller to control the operation of the first and second switches in each half-bridge circuit. Specifically, the PWM signal sent by the controller to any half-bridge circuit may include a first PWM signal and a second PWM signal. The first PWM signal is input to the control terminal of the first switch, causing the first switch to turn on under the control of a valid level of the first PWM signal and turn off under the control of an invalid level of the first PWM signal. Similarly, the second PWM signal is input to the control terminal of the second switch, causing the second switch to turn on under the control of a valid level of the second PWM signal and turn off under the control of an invalid level of the second PWM signal. Furthermore, the first and second PWM signals received by any half-bridge circuit are out of phase, so that the first and second switches in any half-bridge circuit are complementary in their conduction.

[0027] Therefore, in one embodiment of this application, the first to Mth half-bridge circuits can be divided into at least two drive groups, each drive group including at least two half-bridge circuits. Furthermore, at least one half-bridge circuit must be spaced between any two sequentially appearing half-bridge circuits in any drive group. The controller can sequentially send pulse width modulation (PWM) signals to each drive group; that is, after sending a PWM signal to each half-bridge circuit in one drive group, it then sends a PWM signal to each half-bridge circuit in another drive group, performing cyclic control in this manner. Moreover, the PWM signals sent to each half-bridge circuit in each drive group have a sequential phase difference, allowing the half-bridge circuits in the same drive group to output voltage sequentially without simultaneously outputting voltage. This control method, employing interleaved PWM signal transmission, balances the number of high-level phases on both sides of the midpoint of the secondary winding series circuit, reducing secondary voltage accumulation. Furthermore, by combining this control method with an adjustment structure, secondary voltage accumulation can be further reduced.

[0028] In practical applications, the electrical energy output by the magnetically integrated TLVR circuit is supplied to the electrical equipment. However, during operation, the equipment may be in a stable energy consumption state for certain periods, with a relatively stable input current, indicating that the equipment is in a steady state. Based on this, the current at the power supply output terminal can be sampled and compared with a current threshold. If the sampled current is less than the current threshold, it indicates that the equipment is in a steady state and does not require a fast dynamic response. Therefore, in this embodiment, the switching frequency of the PWM signal can be reduced to improve the efficiency of the magnetically integrated TLVR circuit. Based on this, the controller is also configured to, in response to the current at the power supply output terminal being less than the current threshold, control the effective levels of two adjacent first PWM signals output sequentially to have an interval duration.

[0029] In practical applications, electrical equipment may experience sudden loading even in steady state, leading to increased energy consumption and a sudden increase in input current. This indicates that the equipment is in a dynamic state. While the switching frequency of the PWM signal is reduced in steady state to improve efficiency, this reduced frequency results in a poorer dynamic response during sudden loading. Therefore, in this embodiment, the switching frequency of the PWM signal can be increased to improve the dynamic response capability of the magnetically integrated TLVR circuit 120. Based on this, the controller further controls the effective levels of two adjacent first PWM signals in the sequential output to overlap in duration in response to a current at the power output terminal being greater than or equal to a current threshold, and the effective levels of the first and third sequentially output first PWM signals in the sequential output do not overlap in duration.

[0030] During operation, the output current of the half-bridge circuit and the voltage VOUT at the power supply output terminal can be kept stable by adjusting the duty cycle of the first PWM signal in the PWM signal. Based on this, in some embodiments, the measured current of the primary winding of each TLVR inductor and the measured voltage at the power supply output terminal can be collected. The controller adjusts the duty cycle of the PWM signal of the half-bridge circuit corresponding to any TLVR inductor according to the collected measured current of the primary winding of any TLVR inductor and the measured voltage at the power supply output terminal.

[0031] As the switching power supply 100 becomes smaller, the material of the magnetic core 23 gradually changes from ferrite to iron powder core material with high saturation magnetic density. However, the inductance of the iron powder core material exhibits a nonlinear relationship, which brings many difficulties to the control. To address this, in some embodiments, not only are the measured currents of the primary windings and the measured voltages at the power supply output terminals of each TLVR inductor acquired, but the measured currents of the secondary winding series circuits are also acquired. The controller can then send PWM signals to each half-bridge circuit based on the acquired measured currents of the primary windings and secondary winding series circuits of each TLVR inductor, as well as the voltage at the power supply output terminals.

[0032] In some embodiments, several half-bridge circuits near the middle sequence can be selected from the sequentially appearing first to Mth half-bridge circuits. The first or second terminal of the secondary winding corresponding to these half-bridge circuits is connected to the ground terminal. This is equivalent to grounding the secondary winding series circuit near the negative position of the corresponding middle sequence half-bridge circuit, thereby dividing the voltage of the secondary winding series circuit into positive and negative intervals. The voltage can be reduced to a maximum of half the original maximum voltage of the secondary winding series circuit, effectively reducing voltage accumulation in the secondary winding series circuit and benefiting insulation design. Based on this, the controller can simultaneously output PWM signals to each half-bridge circuit, meaning the effective levels of the first PWM signal of each half-bridge circuit have partially or completely overlapping durations. This allows for simultaneous control of the output voltage of each half-bridge circuit, reducing control complexity. Alternatively, the magnetically integrated TLVR circuit can also employ the aforementioned control method to further reduce voltage accumulation in the secondary winding series circuit.

[0033] In some embodiments, the number of half-bridge circuits is even. Connecting the first end of the secondary winding of the TLVR inductor connected to the M / 2 half-bridge circuit to ground halves the maximum voltage in the series circuit of the secondary winding, thereby reducing voltage accumulation. Alternatively, the first end of the secondary winding of the TLVR inductor connected to the half-bridge circuit sequentially adjacent to the M / 2 half-bridge circuit can also be connected to ground, thereby reducing voltage accumulation.

[0034] In some embodiments, the number of half-bridge circuits is odd, and the first end of the secondary winding of the TLVR inductor connected to the (M+1) / 2 half-bridge circuit, or the first end of the secondary winding of the TLVR inductor connected to the half-bridge circuit adjacent to the (M+1) / 2 half-bridge circuit, is connected to ground. This arrangement can reduce voltage accumulation.

[0035] Secondly, embodiments of this application also provide a control method for controlling the magnetically integrated TLVR circuit in the first aspect or any embodiment thereof. Each half-bridge circuit includes a first switch and a second switch connected in series between a power input terminal and a ground terminal. The control terminals of each first switch and the second switch are used to connect to a controller. Multiple half-bridge circuits include sequentially arranged first to M half-bridge circuits, which are divided into at least two drive groups. Each drive group includes at least two half-bridge circuits, and at least one half-bridge circuit is spaced between any two sequentially appearing half-bridge circuits in any drive group. The control method includes: sequentially sending pulse width modulation (PWM) signals to each of the at least two drive groups, with the PWM signals sent to each half-bridge circuit in each drive group having a phase difference. The PWM signals include a first PWM signal and a second PWM signal, the first PWM signal being used to input the control terminal of the first switch, the second PWM signal being used to input the control terminal of the second switch, and the first PWM signal and the second PWM signal received by any half-bridge circuit having opposite phases. This control method allows for the interleaved transmission of PWM signals to balance the number of high-level output phases on both sides of the midpoint of the secondary winding series circuit, reducing secondary voltage accumulation. Furthermore, this control method can be combined with an adjustable structure to further reduce secondary voltage accumulation.

[0036] As switching power supplies become miniaturized, the core material has gradually shifted from ferrite to high-saturation magnetic density iron powder core material. However, the inductance of iron powder core material exhibits a nonlinear relationship, posing many challenges to control. To address this, in some embodiments, PWM signals can be sent to each half-bridge circuit based on the measured current of each primary winding, the measured current of the series circuit, and the measured voltage at the power supply output.

[0037] In some embodiments, the process of sending PWM signals to each half-bridge circuit based on the measured current of each primary winding, the measured current of the series circuit, and the measured voltage at the power supply output terminal may include the following process:

[0038] In the current detection phase, the predicted current of the primary winding of each TLVR inductor is obtained by fitting the measured current of each primary winding, the measured current of the series circuit, the measured voltage of the power supply output terminal, and the switching state of the PWM signal received by each half-bridge circuit.

[0039] The calibration current of the primary winding of each TLVR inductor is determined based on the predicted current and the measured current of the primary winding of each TLVR inductor.

[0040] Based on the calibration current of the primary winding of each TLVR inductor, the duty cycle of the first PWM signal of the half-bridge circuit connected to each TLVR inductor is adjusted, and based on the adjusted duty cycle, the first PWM signal and the second PWM signal are output to the corresponding half-bridge circuit.

[0041] Therefore, unlike ordinary buck circuits where the nonlinear inductance is determined solely by the primary winding current, the nonlinear inductance of the magnetically integrated TLVR circuit in this embodiment is determined jointly by the primary and secondary winding currents. In other words, this embodiment simultaneously detects the primary and secondary winding currents and determines the TLVR inductance based on the total current of both windings. This allows for more accurate current prediction and calibration current based on more precise inductance information, thereby improving the control accuracy of the PWM signal and further enhancing the operational stability and reliability of the magnetically integrated TLVR circuit. Furthermore, this embodiment also includes control functions such as current loop and overcurrent protection based on the calibration current.

[0042] In some embodiments, the process of fitting the predicted current of the primary winding of each TLVR inductor may include the following steps:

[0043] The slope of the current in the series circuit is determined based on the measured current of the series circuit and the switching states of the first and second PWM signals of each half-bridge circuit.

[0044] The slope of the current of the magnetizing inductor of the kth TLVR inductor is determined based on the measured current of the primary winding of the kth TLVR inductor, the measured current of the series circuit, and the switching states of the first PWM signal and the second PWM signal received by the half-bridge circuit connected to the kth TLVR inductor.

[0045] Based on the slope of the current in the determined series circuit, the slope of the current in the magnetizing inductance of the kth TLVR inductor, and the calibration current of the primary winding of the kth TLVR inductor determined in the previous detection stage, the predicted current of the primary winding of the kth TLVR inductor in the current detection stage is obtained by fitting.

[0046] With this setup, the predicted current can be obtained by determining the slope of the current in the series circuit.

[0047] In some embodiments, the process of determining the slope of the current in the series loop based on the measured current of the series loop and the switching states of the first PWM signal and the second PWM signal of each half-bridge circuit may include the following process:

[0048] Determine the inductance of the compensation circuit based on the measured current of the series circuit;

[0049] The slope of the current in the series circuit is determined based on the switching states of the first and second PWM signals received by each half-bridge circuit and the inductance of the compensation circuit inductor.

[0050] With this setup, the slope of the current in the series circuit can be calculated.

[0051] In some embodiments, the process of determining the slope of the current in the magnetizing inductor of the kth TLVR inductor based on the measured current of the primary winding of the kth TLVR inductor, the measured current of the series circuit, and the switching states of the first PWM signal and the second PWM signal received by the half-bridge circuit connected to the kth TLVR inductor may include the following process:

[0052] Determine the inductance of the magnetizing inductor of the kth TLVR based on the measured current of the kth TLVR inductor and the measured current of the series circuit.

[0053] Based on the switching states of the first and second PWM signals received by the half-bridge circuit connected to the k-th TLVR inductor and the determined inductance of the magnetizing inductor of the k-th TLVR inductor, the slope of the current of the magnetizing inductor of the k-th TLVR inductor is determined.

[0054] With this setup, the slope of the current in the magnetizing inductance of the kth TLVR inductor can be calculated.

[0055] In some embodiments, the control method further includes controlling the effective levels of two adjacent first PWM signals output sequentially to have an interval duration in response to the current at the power supply output being less than a current threshold, so as to improve the efficiency of the magnetically integrated TLVR circuit.

[0056] In some embodiments, the control method further includes controlling the effective levels of two adjacent first PWM signals output sequentially to have an overlap duration in response to the current at the power supply output terminal being greater than or equal to a current threshold, and controlling the effective levels of the first PWM signal output in the first sequence and the first PWM signal output in the third sequence of the three adjacent first PWM signals output sequentially to not have an overlap duration, so as to improve dynamic response capability.

[0057] Thirdly, embodiments of this application also provide a switching power supply, which includes a controller and one or more magnetically integrated TLVR circuits. The controller is connected to each half-bridge circuit in the magnetically integrated TLVR circuit and is used to output PWM signals to each half-bridge circuit to control the operation of each half-bridge circuit. Furthermore, the magnetically integrated TLVR circuit is the magnetically integrated TLVR circuit of the first aspect or any embodiment of the first aspect described above.

[0058] Fourthly, embodiments of this application also provide an electronic device, which includes a switching power supply and a power supply device. The output terminal of the switching power supply is connected to the power-consuming device to supply power to the power-consuming device.

[0059] Furthermore, the technical effects of the corresponding solutions in the third and fourth aspects can be referenced from the technical effects that can be obtained by the corresponding solutions in the first and second aspects, and the repetitions will not be detailed. Attached Figure Description

[0060] Figure 1 A structural block diagram of an electronic device provided in an embodiment of this application;

[0061] Figure 2 A schematic diagram of a circuit structure for a magnetically integrated TLVR circuit provided in an embodiment of this application;

[0062] Figure 3 for Figure 2 The equivalent circuit diagram of the magnetically integrated TLVR circuit is shown below.

[0063] Figure 4 for Figure 2 The equivalent winding diagram of the primary and secondary windings of each magnetically integrated TLVR inductor in the magnetically integrated TLVR circuit shown.

[0064] Figure 5 for Figure 2 The diagram shows the equivalent schematic of the primary winding, secondary winding, and magnetic flux of a magnetically integrated TLVR inductor in the magnetically integrated TLVR circuit shown.

[0065] Figure 6a A top view of the structure of a magnetically integrated TLVR inductor provided in an embodiment of this application;

[0066] Figure 6b for Figure 6a A schematic diagram of the cross-sectional structure along the AA' direction;

[0067] Figure 6c for Figure 6a A schematic diagram of the cross-sectional structure along the BB' direction;

[0068] Figure 7a A three-dimensional structural diagram of the primary and secondary windings in a TLVR inductor provided in an embodiment of this application;

[0069] Figure 7b for Figure 7a A schematic diagram of the cross-sectional structure along the AA' direction;

[0070] Figure 8a A three-dimensional structural schematic diagram of a magnetically integrated TLVR inductor provided in an embodiment of this application;

[0071] Figure 8b for Figure 8a A schematic diagram of the cross-sectional structure along the AA' direction;

[0072] Figure 9a Another three-dimensional structural schematic diagram of the magnetically integrated TLVR inductor provided in the embodiments of this application;

[0073] Figure 9b for Figure 9a A schematic diagram of the cross-sectional structure along the AA' direction;

[0074] Figure 10a A schematic diagram of another three-dimensional structure of the magnetically integrated TLVR inductor provided in an embodiment of this application;

[0075] Figure 10b for Figure 10a A schematic diagram of the cross-sectional structure along the AA' direction;

[0076] Figure 11 This is a schematic diagram of the structure of the magnetically integrated TLVR circuit and controller provided in the embodiments of this application;

[0077] Figure 12 A schematic diagram of a half-bridge circuit receiving a PWM signal, provided in an embodiment of this application;

[0078] Figure 13 A schematic diagram of a specific structure of a magnetically integrated TLVR circuit provided in an embodiment of this application;

[0079] Figure 14a for Figure 13 A timing diagram of the PWM signal for the magnetically integrated TLVR circuit shown;

[0080] Figure 14b for Figure 13 Another timing diagram of the PWM signal of the magnetic integrated TLVR circuit 120 shown;

[0081] Figure 15 This is a flowchart of the control method for the magnetically integrated TLVR circuit in the embodiments of this application;

[0082] Figure 16 A schematic diagram of another circuit structure of the magnetically integrated TLVR circuit provided in the embodiments of this application;

[0083] Figure 17a for Figure 16 A simulated voltage diagram;

[0084] Figure 17b This is a simulated voltage diagram of the magnetically integrated TLVR circuit in the embodiments of this application when physical components are used as the inductors of the compensation loop.

[0085] Figure 18a A schematic diagram of another three-dimensional structure of the magnetically integrated TLVR inductor provided in the embodiments of this application;

[0086] Figure 18b for Figure 18a A schematic diagram of the cross-sectional structure along the AA' direction;

[0087] Figure 19 A schematic diagram of another circuit structure of the magnetically integrated TLVR circuit provided in the embodiments of this application;

[0088] Figure 20 for Figure 19 A simulated voltage diagram;

[0089] Figure 21 This is a schematic diagram of another circuit structure of the magnetically integrated TLVR circuit provided in the embodiments of this application. Detailed Implementation

[0090] To make the objectives, technical solutions, and advantages of this application clearer, the application will be further described in detail below with reference to the accompanying drawings. The specific operational methods in the method embodiments can also be applied to the device embodiments or system embodiments. It should be noted that in the description of this application, "at least one" refers to one or more, where "multiple" refers to two or more. Therefore, in the embodiments of this application, "multiple" can also be understood as "at least two". "And / or" describes the relationship between related objects, indicating that three relationships can exist. For example, A and / or B can represent: A existing alone, A and B existing simultaneously, and B existing alone. Furthermore, the character " / ", unless otherwise specified, generally indicates that the preceding and following related objects have an "or" relationship. And, words such as "first" and "second" are only used for distinguishing the purpose of description and should not be construed as indicating or implying relative importance or order. In addition, in the embodiments of this application, "connection" refers to electrical connection; the connection between two electrical components can be a direct connection between the two electrical components or an indirect connection through an intermediate medium. For example, A and B can be connected directly, or indirectly through one or more other electrical components, such as A and B being connected. Alternatively, A can be directly connected to C, C can be directly connected to B, and A and B can be connected through C.

[0091] It should be noted that the same reference numerals in the accompanying drawings of this application denote the same or similar structures, and therefore repeated descriptions of them will be omitted. Terms expressing position and direction described in this application are illustrative based on the accompanying drawings, but may be modified as needed, and all modifications are included within the scope of protection of this application. The accompanying drawings of this application are for illustrating relative positional relationships only and do not represent actual scale.

[0092] To facilitate understanding of the switching power supply, power supply method, power supply equipment, and data center equipment provided in the embodiments of this application, their application scenarios will be introduced first below.

[0093] The magnetically integrated TLVR circuit provided in this application embodiment can be applied to any switching power supply that performs direct current (DC) voltage conversion. The switching power supply can be applied to electronic devices that require power to supply power to the devices (i.e., loads) within the electronic device. Exemplarily, electronic devices include, but are not limited to, data center equipment and information communication technology (ICT) equipment. Devices include, but are not limited to, computing chips. Of course, the switching power supply can also be applied to other devices (e.g., servers), and is not limited thereto. The magnetically integrated TLVR circuit, switching power supply, and data center equipment provided in this application embodiment will be described below with reference to the accompanying drawings.

[0094] Figure 1 A structural block diagram of an electronic device provided in an embodiment of this application, referring to... Figure 1 Electronic device 1 may include a power supply device 11 and a power consumption device 12. The power supply device 11 may include a power supply 200 and a switching power supply 100. The input terminal of the power supply 200 is used to receive power supply voltage, and the output terminal of the power supply 200 is connected to the input terminal of the switching power supply 100. The output terminal of the switching power supply 100 is connected to the power consumption device 12. The power supply voltage can be AC ​​mains power or DC power output from an energy storage device. The power supply 200 can boost or buck the power supply voltage to convert it into DC power before outputting it to the switching power supply 100. The switching power supply 100 bucks the received DC power and outputs it to the power consumption device 12 to supply power to the device 12. Exemplary examples include, but are not limited to, computing chips, including but not limited to, ASICs, CPUs, GPUs, field-programmable gate arrays (FPGAs), general-purpose processors, digital signal processing (DSPs), or other programmable logic devices, transistor logic devices, hardware components, or any combination thereof, or devices capable of implementing or executing the various exemplary logic blocks, modules, and circuits described in connection with the disclosure of this application. The aforementioned computing device 12 may also be a combination of computing chips, such as a combination of one or more microprocessors, a combination of a DSP and a microprocessor, etc.

[0095] TLVR circuits, with their advantages of fast transient response and reduced back-end capacitor costs, are widely used in switching power supplies, becoming the mainstream circuit for rapidly responding to load fluctuations in low-voltage, high-current applications. Currently, one type of TLVR circuit uses discrete TLVR inductors, resulting in a large overall TLVR inductor size, which is detrimental to miniaturizing and modularizing the switching power supply for placement near computing chips. Another type of TLVR circuit integrates the TLVR inductor, but this integration achieves negative coupling, weakening the dynamic performance of the TLVR circuit and making the core prone to saturation due to current imbalance, posing a risk of core burnout. However, to reduce the risk of core saturation, the core width needs to be increased, resulting in a larger core size and consequently a larger integrated TLVR inductor size, which also hinders miniaturization and modularization of the switching power supply for placement near computing chips. Furthermore, for the negative coupling-based inductor integration method, several phases of the half-bridge circuit coupled by the same negative coupling inductor must be switched in or out simultaneously, resulting in inflexible phase switching. Therefore, this application provides a magnetically integrated TLVR circuit that can reduce the overall size of the TLVR inductor while achieving high dynamic response based on flexible control methods. This facilitates the miniaturization and modularization of the switching power supply for placement closer to the computing chip.

[0096] The magnetically integrated TLVR circuit provided in this application embodiment can be applied to switching power supplies. While achieving high dynamic response, it facilitates the miniaturization and modularization of the switching power supply for placement closer to the computing chip. For example, refer to... Figure 1 The switching power supply 100 may include a magnetically integrated TLVR circuit 120 and a controller 110. The power input terminal VIN of the magnetically integrated TLVR circuit 120 can be connected to the input terminal of the switching power supply, and the power output terminal VOUT of the magnetically integrated TLVR circuit 120 can be connected to the output terminal of the switching power supply. Furthermore, the controller 110 is connected to the magnetically integrated TLVR circuit 120, and can control the operation of the magnetically integrated TLVR circuit 120 so that the magnetically integrated TLVR circuit 120 steps down the received DC power and converts it back to DC power before outputting it to the power-consuming equipment. This allows the magnetically integrated TLVR circuit 120 provided in this embodiment to be suitable for low-voltage, high-current applications.

[0097] The structure and operation of the magnetically integrated TLVR circuit provided in the embodiments of this application will be described in detail below with reference to the accompanying drawings.

[0098] Figure 2 A schematic diagram of a magnetically integrated TLVR circuit provided in an embodiment of this application is shown below. Figure 2The magnetically integrated TLVR circuit 120 provided in this application embodiment may include multiple half-bridge circuits 121_1 to 121_M (K is a positive integer greater than 1) and multiple TLVR inductors 122_1 to 122_M. The first terminal of any half-bridge circuit 121_1 to 121_M is connected to the power input terminal VIN, and the second terminal of any half-bridge circuit 121_1 to 121_M is connected to the ground terminal GND. Furthermore, each TLVR inductor 122_1 to 122_M may include a magnetic core, as well as a primary winding 21 and a secondary winding 22 wound on the magnetic core. The plurality of TLVR inductors 122_1 to 122_M correspond one-to-one with the plurality of half-bridge circuits 121_1 to 121_M. The switching node of any half-bridge circuit 121_1 to 121_M is connected to the first end of the primary winding 21 of the corresponding TLVR inductor 122_1 to 122_M, and the second end of the primary winding 21 of any TLVR inductor 122_1 to 122_M is connected to the power output terminal VOUT.

[0099] Furthermore, the plurality of half-bridge circuits 121_1 to 121_M include a first half-bridge circuit 121_1 to an Mth half-bridge circuit 121_M arranged sequentially. The second end of the secondary winding 22 of the TLVR inductor 122_1 connected to the first half-bridge circuit 121_1 is interconnected with the first end of the secondary winding 22 of the TLVR inductor 122_M connected to the Mth half-bridge circuit 121_M. The first end of the secondary winding 22 of the TLVR inductor 122_1 connected to the first half-bridge circuit 121_1 is connected with the second end of the secondary winding 22 of the TLVR inductor 122_2 connected to the second half-bridge circuit 121_2, and so on. The first end of the secondary winding 22 of the TLVR inductor 122_M-1 connected to the M-1th half-bridge circuit 121_M-1 is connected with the second end of the secondary winding 22 of the TLVR inductor 122_M connected to the Mth half-bridge circuit 121_M. Therefore, the secondary windings 22 of the multiple TLVR inductors 122_1 to 122_M are connected end to end to form a series circuit, and this series circuit is connected to the ground terminal GND to achieve grounding. Furthermore, a compensation circuit inductor is connected in series with the series circuit. By designing a suitable inductance value for the compensation circuit inductor, high steady-state inductance (Lss) and low transient inductance (Ltr) are achieved, resulting in low current ripple, high efficiency, and high transient response speed.

[0100] Furthermore, based on grouping at least two sequentially adjacent half-bridge circuits into a circuit group, the first half-bridge circuit 121_1 to the Mth half-bridge circuit 121_M are divided into circuit groups 131_1 to 131_N. Each circuit group 131_1 to 131_N may include at least two sequentially adjacent half-bridge circuits. Additionally, the TLVR inductors connected to each half-bridge circuit in any circuit group 131_1 to 131_N share a common magnetic core 23 to form a single magnetically integrated TLVR inductor 132_1 to 132_N. Moreover, in any magnetically integrated TLVR inductor 132_1 to 132_N, the winding direction of each primary winding 21 from the first end to the second end is the same as the winding direction of each secondary winding 22 from the first end to the second end. For example, taking any circuit group 131_1 to 131_N as having two sequentially adjacent half-bridge circuits, circuit group 131_1 includes a first half-bridge circuit 121_1 and a second half-bridge circuit 121_2. Then, TLVR inductors 122_1 and TLVR inductors 122_2 are integrated to form a magnetically integrated TLVR inductor 132_1. In the magnetically integrated TLVR inductor 132_1, the winding directions of the primary winding 21 and the secondary winding 22 of TLVR inductors 122_1 and TLVR inductors 122_2 from the first end to the second end are the same. ...Circuit group 131_N includes the (M-1)th half-bridge circuit 121_M-1 and the Mth half-bridge circuit 121_M. The TLVR inductors 122_M-1 and 122_M are integrated to form a magnetically integrated TLVR inductor 132_N. In the magnetically integrated TLVR inductor 132_N, the primary winding 21 and secondary winding 22 of the TLVR inductors 122_M-1 and 122_M have the same winding direction from the first end to the second end. The rest can be deduced similarly and will not be elaborated further here.

[0101] Figure 3 for Figure 2 The equivalent circuit diagram of the magnetically integrated TLVR circuit shown is as follows. Figure 4 for Figure 2 The diagram shows the equivalent winding diagrams of the primary and secondary windings of each magnetically integrated TLVR inductor in the magnetically integrated TLVR circuit shown, combined with... Figures 2 to 4 In this embodiment of the application, taking any circuit group 131_1 to 131_N including two sequentially adjacent half-bridge circuits as an example, since the winding direction of the primary winding 21 of TLVR inductor 122_1 and TLVR inductor 122_2 from the first end to the second end is the same, when current is input to the first end of the primary winding 21 of TLVR inductor 122_1 and TLVR inductor 122_2, the magnetic field generated by the primary winding 21 of TLVR inductor 122_1 and TLVR inductor 122_2 can be made to have the same direction. Therefore, the mutual inductance coupling coefficient K between the primary winding 21 of TLVR inductor 122_1 and TLVR inductor 122_2 is also the same. pp1Greater than zero, and the coupling coefficient K pp1 The coupling coefficient K between the primary windings 21 of TLVR inductors 122_1 and 122_2 is relatively small, resulting in a weak positive coupling. This reduces interference between the primary windings 21 of TLVR inductors 122_1 and 122_2. When current is input to the first terminal of the primary windings 21 of TLVR inductors 122_M-1 and 122_M, the magnetic fields generated by the primary windings 21 of TLVR inductors 122_M-1 and 122_M are in the same direction, thus the coupling coefficient K between the primary windings 21 of TLVR inductors 122_M-1 and 122_M is equal. ppN It is also greater than zero, and the coupling coefficient K ppN The coupling is also relatively small, resulting in a weak positive coupling between the primary windings 21 of TLVR inductor 122_M-1 and TLVR inductor 122_M, which reduces interference between them. The same principle applies to other cases, and will not be elaborated further here. Based on this, in the embodiments of this application, by integrating at least two TLVR inductors to form a magnetically integrated TLVR inductor, and by making the ports of the primary windings 21 connecting the output terminals of each half-bridge circuit 121_1 to 121_M the first terminals, and by making the winding direction of each primary winding 21 in any magnetically integrated TLVR inductor 132_1 to 132_N the same from the first terminal to the second terminal, when current is input to the first terminal of each primary winding 21, the magnetic field direction generated by each primary winding 21 can be the same, thereby forming a weak positive coupling between different primary windings 21 in any magnetically integrated TLVR inductor 132_1 to 132_N, thereby reducing the interference between different primary windings 21 in any magnetically integrated TLVR inductor 132_1 to 132_N.

[0102] Furthermore, continue to combine Figures 2 to 4 In this embodiment, the winding directions from the first end to the second end of the primary winding 21 and the secondary winding 22 of any TLVR inductor 122_1 to 122_M are also the same. This ensures that when current is input to the first end of the primary winding 21 and the first end of the secondary winding 22 of any TLVR inductor 122_1 to 122_M, the magnetic field directions generated are the same, i.e., the mutual inductance coupling coefficient K is equal. ps It is also greater than zero, and the coupling coefficient K psThe secondary windings are relatively large, thus enabling strong positive coupling between the primary winding 21 and secondary winding 22 of any TLVR inductor 122_1 to 122_M. Furthermore, since the secondary windings 22 of the TLVR inductors 122_1 to 122_M are connected in series, the output current slope is increased and the equivalent output inductance is reduced through dynamic linkage of the secondary windings. Additionally, changes in load current can have a faster impact on any half-bridge circuit 121_1 to 121_M, resulting in a faster transient response.

[0103] also, Figure 5 for Figure 2 The diagram shows the equivalent windings of the primary and secondary windings and the magnetic flux of a magnetically integrated TLVR inductor in the magnetically integrated TLVR circuit. Figures 2 to 5 The arrows on the primary winding 21 and secondary winding 22 of the TLVR inductors 122_1 to 122_M represent the direction of the current. Taking the magnetically integrated TLVR inductor 132_1 as an example, when the input current is applied, the direction of the magnetic flux Φ1 generated by the TLVR inductor 122_1 (i.e., the direction of the arrow on the dashed line) is opposite to the direction of the magnetic flux Φ2 generated by the TLVR inductor 122_2 (i.e., the direction of the arrow on the dashed line) in the common magnetic core 23 region GB. Therefore, the magnetic flux in this region GB can be partially or completely canceled out. Based on this, in the embodiments of this application, based on the connection method of the above-mentioned half-bridge circuits 121_1~121_M and TLVR inductors 122_1~122_M, and the winding direction of the primary winding 21 and secondary winding 22 in any magnetic integrated TLVR inductor, when the magnetic integrated TLVR circuit 120 is working, the magnetic flux in the common magnetic core 23 region between adjacent TLVR inductors can be partially or completely canceled, thereby reducing the volume of the common magnetic core 23 region, and further reducing the volume of the magnetic core 23 of the magnetic integrated TLVR inductor, which is beneficial to reducing the overall volume of the magnetic integrated TLVR inductor and reducing the loss of the magnetic integrated TLVR inductor.

[0104] Understandably, the number of half-bridge circuits in any circuit group can be 2, 3, 4, or more; that is, the number of TLVR inductors in any magnetically integrated TLVR inductor can be 2, 3, 4, or more, which can be determined according to the actual application scenario and is not limited here. Furthermore, there can be one or more circuit groups. When there are multiple circuit groups, the number of half-bridge circuits in these multiple circuit groups can be the same or different, or the number of half-bridge circuits in these multiple circuit groups can be partially the same or partially different.

[0105] In the embodiments of this application, the primary winding 21 and secondary winding 22 can be wound on the magnetic core 23 to achieve their functions. In some embodiments of this application, reference is made to... Figures 6a to 6c , Figure 6a This is a top view of the magnetically integrated TLVR inductor provided in an embodiment of this application. Figure 6b for Figure 6a A schematic diagram of the cross-sectional structure along the AA' direction. Figure 6c for Figure 6a The cross-sectional view along the BB' direction shows that, taking the magnetically integrated TLVR inductor 132_1 as an example, the primary winding 21 of TLVR inductors 122_1 to 122_2 can be wound half a turn on the magnetic core 23, and the winding direction of the first end to the second end of the primary winding 21 is the same. After winding half a turn, it is connected to the switching node and power output terminal VOUT of the corresponding half-bridge circuit, respectively. The rest are similar and can be deduced by analogy, which will not be elaborated here. In some other embodiments of this application, the primary winding 21 of any TLVR inductor can also be wound one, two or more turns on the magnetic core 23 and then connected to the switching node and power output terminal VOUT of the corresponding half-bridge circuit, respectively.

[0106] Continue to refer to Figures 6a to 6c In some embodiments of this application, taking the magnetically integrated TLVR inductor 132_1 as an example, the secondary winding 22 of TLVR inductors 122_1 to 122_2 can also be wound half a turn on the magnetic core 23, and the winding direction from the first end to the second end of the secondary winding 22 is the same, and after winding half a turn, it is connected to the other secondary windings 22 respectively. The rest are similar, and can be deduced by analogy, without further details here. In other embodiments of this application, the secondary winding 22 of any TLVR inductor can also be wound one, two, or more turns on the magnetic core 23 and then connected to the other secondary windings 22 respectively.

[0107] In specific implementations, based on the arrangement that the primary winding 21 and the secondary winding 22 have the same winding direction, various implementation methods can be used to wind the primary winding 21 and the secondary winding 22 of any TLVR inductor onto the magnetic core 23. In some embodiments of this application, refer to Figures 6a to 6cContinuing with the example of the magnetically integrated TLVR inductor 132_1, in TLVR inductor 122_1, the secondary winding 22 is wound on the magnetic core 23, and the primary winding 21 is wound on the secondary winding 22. The first ends of the primary winding 21 and the secondary winding 22 are located on one side, and the second ends are located on the other side, thus ensuring that the winding directions of the primary winding 21 and the secondary winding 22 are the same. Furthermore, in TLVR inductor 122_1, an insulating layer 24 is provided between the primary winding 21 and the secondary winding 22 to prevent short circuits. Based on this, the primary winding 21 and the secondary winding 22 in TLVR inductor 122_1 can form a nested structure. Similarly, the primary winding 21 and the secondary winding 22 in other TLVR inductors also form a nested structure. By winding the primary winding 21 of any TLVR inductor onto the secondary winding 22, the space occupied by each TLVR inductor can be further reduced. Furthermore, the nested structures in any magnetically integrated TLVR inductor can be arranged sequentially at intervals along the extension direction F1 of the magnetic core 23. Combined with the aforementioned half-bridge circuit and TLVR inductor connection method, after current is input to the primary winding 21 and secondary winding 22, the magnetic flux in the common magnetic core 23 between adjacent nested structures can be partially or completely canceled out. Therefore, the spacing between adjacent nested structures can be set smaller, thereby further reducing the volume of the magnetically integrated TLVR inductor.

[0108] It is understandable that the insulating layer 24 can be configured as a gas gap, an insulating material film layer, etc., and is not limited here.

[0109] Continue to refer to Figures 6a to 6c Taking the TLVR inductor 122_1 as an example, the primary winding 21 can have a sheet-like first U-shaped structure U1, and the secondary winding 22 has a sheet-like second U-shaped structure U2. The second U-shaped structure U2 is disposed in the accommodating cavity of the first U-shaped structure U1, and the opening directions of the second U-shaped structure U2 and the first U-shaped structure U1 are the same, thus forming a nested structure between the primary winding 21 and the secondary winding 22. With this configuration, since the first U-shaped structure U1 and the second U-shaped structure U2 are only tightly attached by an insulating layer 24 and do not contain any magnetically conductive material, the distance between the two U-shaped structures is very close yet electrically isolated, allowing for strong coupling between the first U-shaped structure U1 and the second U-shaped structure U2. Furthermore, since the sheet-like first U-shaped structure U1 and the second U-shaped structure U2 have good connection strength, the connection stability of the inductor device can be improved.

[0110] To improve the reliability and stability of the connection between the opening of the first U-shaped structure U1 and the half-bridge circuit and the ground terminal GND, pins can be extended from both ends of the opening of the first U-shaped structure U1 for connection via pins. For example, refer to... Figure 7a and Figure 7b , Figure 7a This is a three-dimensional structural diagram of the primary and secondary windings in a TLVR inductor provided in an embodiment of this application. Figure 7b for Figure 7a A cross-sectional view along the AA' direction shows that in any TLVR inductor, the primary winding 21 also has a sheet-like first pin P1 and a sheet-like second pin P2. The first pin P1 is connected to one end of the first U-shaped structure U1 and extends outwards towards the opening of the first U-shaped structure U1. The second pin P2 is connected to the other end of the first U-shaped structure U1 and also extends outwards towards the opening of the first U-shaped structure U1. The first pin P1 can be used as the first terminal to connect to the switching node of the half-bridge circuit, and the second pin P2 can be used as the second terminal to connect to the ground terminal GND. This configuration improves the connection stability of the inductor device because the sheet-like first pin P1 and sheet-like second pin P2 have good connection strength.

[0111] To improve the reliability and stability of the connection between the opening of the second U-shaped structure U2 and the half-bridge circuit and the ground terminal GND, pins can be extended from both ends of the opening of the second U-shaped structure U2 for connection via pins. For example, refer to... Figure 7a and Figure 7b In any TLVR inductor, the secondary winding 22 also has a chip-shaped third pin P3 and a chip-shaped fourth pin P4. The third pin P3 is connected to one end of the second U-shaped structure U2 and extends towards the inside of the opening of the second U-shaped structure U2. The fourth pin P4 is connected to the other end of the second U-shaped structure U2 and also extends towards the inside of the opening of the second U-shaped structure U2. The third pin P3 can be used as the first end, and the fourth pin P4 as the second end, so that the third pin P3 can be connected to the fourth pin P4 of the secondary winding 22 of one TLVR inductor, and the fourth pin P4 can be connected to the third pin P3 of the secondary winding 22 of another TLVR inductor. This configuration improves the connection stability of the inductor device because the chip-shaped third pin P3 and the chip-shaped fourth pin P4 have good connection strength.

[0112] Furthermore, referring to Figure 7a and Figure 7b In any TLVR inductor, the first pin P1 and the third pin P3 are separated by a gap to achieve insulation, and the second pin P2 and the fourth pin P4 are separated by a gap to achieve insulation.

[0113] In specific implementations, the first U-shaped structure U1, the first pin P1, and the second pin P2 in any primary winding 21 can be integrally formed from the same material. Similarly, the second U-shaped structure U2, the third pin P3, and the fourth pin P4 in any secondary winding 22 can also be integrally formed from the same material. For example, the primary winding 21 and secondary winding 22 can be formed by bending a conductive metal sheet. It is worth noting that in practical applications, the primary winding 21 and secondary winding 22 can also be linear or other shapes, including irregular shapes, without affecting the implementation of this application. Furthermore, the connection between the first pin P1 and the second pin P2 and the first U-shaped structure U1 is a bent shape, which can reduce the stress at the connection between the first pin P1 and the second pin P2 and the first U-shaped structure U1, improving stability. Furthermore, the connections between the third pin P3 and the fourth pin P4 and the second U-shaped structure U2 are curved, which can reduce the stress at the connection points and improve stability. Of course, the connections between the first pin P1 and the second pin P2 and the first U-shaped structure U1, as well as the connections between the third pin P3 and the fourth pin P4 and the second U-shaped structure U2, can also be designed as broken lines; this is not limited here.

[0114] Furthermore, the primary winding 21 and secondary winding 22 of any magnetically integrated TLVR inductor can be embedded within the magnetic core 23 to improve their bonding tightness, and the magnetic core 23 is used to protect the primary winding 21 and secondary winding 22. For example, refer to... Figure 8a and Figure 8b , Figure 8a This is a three-dimensional structural diagram of a magnetically integrated TLVR inductor provided in an embodiment of this application. Figure 8b for Figure 8a The cross-sectional view along the AA' direction, taking the magnetically integrated TLVR inductor 132_1 as an example, shows that the nested structure formed by the primary winding 21 and secondary winding 22 of TLVR inductors 122_1 to 122_2 is arranged sequentially at intervals along the extension direction F1 of the magnetic core 23. Furthermore, the primary winding 21 and secondary winding 22 of TLVR inductors 122_1 to 122_2 are both embedded within the magnetic core 23, so as to protect the primary winding 21 and secondary winding 22 of TLVR inductors 122_1 to 122_2 through the magnetic core 23, and to improve the tightness of the connection between the magnetic core 23 and the primary winding 21 and secondary winding 22 of TLVR inductors 122_1 to 122_2.

[0115] In practical implementation, a one-piece die-casting process can be used to die-cast the TLVR inductor within each integrated magnetic TLVR inductor, thus making each integrated magnetic TLVR inductor a one-piece structure. Since the one-piece die-casting process uses a mold for direct molding, it avoids errors and deformation problems that may exist in traditional processing, thereby improving the accuracy and quality of the integrated magnetic TLVR inductor. Furthermore, the one-piece die-casting process is highly automated, significantly improving production efficiency and reducing labor and material costs. In addition, because the one-piece die-casting process eliminates the need for multiple steps, it also saves manufacturing time.

[0116] The magnetic cores in the embodiments of this application include, but are not limited to, magnetic cores made of ferrite or magnetic powder cores made of one or more of metallic, amorphous, and nanocrystalline magnetic materials. Of course, in practical applications, the magnetic cores can also be made of other materials, and this application does not limit this.

[0117] Heat is generated when current is transmitted between the primary winding 21 and the secondary winding 22. If this heat cannot be dissipated in time, it will affect the overall performance of the device. In the embodiments of this application, reference is made to... Figure 9a and Figure 9b , Figure 9a This is a schematic diagram of another three-dimensional structure of the magnetically integrated TLVR inductor provided in an embodiment of this application. Figure 9b for Figure 9a The cross-sectional view along the AA' direction illustrates how, to improve the heat dissipation of the magnetically integrated TLVR inductor, taking the magnetically integrated TLVR inductor 132_1 as an example, the upper surface S1 of the first U-shaped structure U1 in TLVR inductors 122_1 to 122_2, facing away from its opening, can be exposed outside the magnetic core 23. This configuration allows the heat generated by the primary winding 21 and secondary winding 22 to be directly conducted to the air through the upper surface S1, improving the heat dissipation of the magnetically integrated TLVR inductor 132_1. In practical implementation, some or all of the magnetically integrated TLVR inductors can be configured in the same way as the magnetically integrated TLVR inductor 132_1; this is not limited here.

[0118] To further improve the heat dissipation performance of magnetically integrated TLVR inductors, refer to Figure 10a and Figure 10b , Figure 10a This is another three-dimensional structural schematic diagram of the magnetically integrated TLVR inductor provided in the embodiments of this application. Figure 10b for Figure 10aThe cross-sectional view along the AA' direction, taking the magnetically integrated TLVR inductor 132_1 as an example, shows that the magnetic core 23 protrudes from the side facing away from the opening of the first U-shaped structure U1 of each primary winding 21. This is equivalent to adding a protrusion TB to the side of the magnetic core 23 facing away from the opening of the first U-shaped structure U1 of each primary winding 21, thereby increasing the surface area of ​​the magnetic core 23 on the side facing away from the opening of the first U-shaped structure U1 of each primary winding 21, and further improving the heat dissipation effect of the magnetically integrated TLVR inductor 132_1. In specific implementations, some or all of the magnetically integrated TLVR inductors can be configured in the same way as the magnetically integrated TLVR inductor 132_1; this is not limited here.

[0119] In a specific implementation, the controller 110 can be connected to each half-bridge circuit 121_1 to 121_M, thereby controlling the operation of each half-bridge circuit 121_1 to 121_M through the controller 110, which can realize step-down conversion, so that the magnetic integrated TLVR circuit 120 provided in this application embodiment can be adapted to low-voltage and high-current application scenarios.

[0120] Figure 11 This is a schematic diagram of the structure of the magnetically integrated TLVR circuit and controller provided in the embodiments of this application, with reference to... Figure 11 The controller 110 can be connected to each half-bridge circuit 121_1 to 121_M. During operation, the controller 110 outputs pulse width modulation (PWM) signals SQ_1 to SQ_M to each half-bridge circuit 121_1 to 121_M to control the operation of each half-bridge circuit 121_1 to 121_M. Combined with the TLVR inductors 122_1 to 122_M, the step-down conversion operation can be realized.

[0121] For example, each half-bridge circuit 121_1 to 121_M may include a first switch Qa and a second switch Qb connected in series between the power input terminal VIN and the ground terminal GND. For instance, the first terminal of the first switch Qa is connected to the power input terminal VIN, and the first terminal of the second switch Qb is connected to the ground terminal GND. The second terminals of the first switch Qa and the second switch Qb in each half-bridge circuit 121_1 to 121_M are interconnected at a switching node. Furthermore, the control terminals of each first switch Qa and the second switch Qb are respectively connected to a controller 110, so that the controller 110 can control the operation of the first switch Qa and the second switch Qb in each half-bridge circuit 121_1 to 121_M. It is understood that the switch in the embodiments of this application can be one or more of various types of switching devices, such as relays, metal oxide semiconductor field effect transistors (MOSFETs), bipolar junction transistors (BJTs), insulated gate bipolar transistors (IGBTs), and silicon carbide (SiC) MOSFETs. These will not be listed individually in the embodiments of this application. Furthermore, each switch can include a first terminal, a second terminal, and a control terminal, wherein the control terminal is used to control the closing or opening of the switch. When the switch is closed, current can be transferred between the first terminal and the second terminal. When the switch is open, no current can be transferred between the first terminal and the second terminal. Taking a MOSFET as an example, the control terminal of the switch is the gate, the first terminal of the switch can be the source, and the second terminal can be the drain, or the first terminal can be the drain and the second terminal can be the source.

[0122] When the magnetically integrated TLVR circuit 120 is operating, the PWM signal sent by the controller 110 to either half-bridge circuit may include a first PWM signal and a second PWM signal. The first PWM signal is used to input the control terminal of the first switch Qa, thereby causing the first switch Qa to conduct under the control of the effective level of the first PWM signal and to turn off under the control of the ineffective level of the first PWM signal. Similarly, the second PWM signal is used to input the control terminal of the second switch Qb, thereby causing the second switch Qb to conduct under the control of the effective level of the second PWM signal and to turn off under the control of the ineffective level of the second PWM signal. Furthermore, the first PWM signal and the second PWM signal received by either half-bridge circuit are out of phase, so that the first switch Qa and the second switch Qb in either half-bridge circuit are complementary in conduction. For example, taking half-bridge circuit 121_1 as an example, refer to... Figure 11 and Figure 12 , Figure 12This is a schematic diagram of a half-bridge circuit receiving a PWM signal according to an embodiment of this application. The PWM signal SQ_1 sent by the controller 110 to the half-bridge circuit 121_1 may include a first PWM signal Sa_1 and a second PWM signal Sb_1. The first PWM signal Sa_1 is input to the control terminal of the first switch Qa to control the conduction and disconnection of the first switch Qa. The second PWM signal Sb_1 is input to the control terminal of the second switch Qb to control the conduction and disconnection of the second switch Qb. Furthermore, the first PWM signal Sa_1 and the second PWM signal Sb_1 are out of phase, so that the first switch Qa and the second switch Qb in the half-bridge circuit 121_1 can be complementary in conduction.

[0123] It is worth mentioning that this embodiment uses the example of the first PWM signal and the second PWM signal having an effective level of high and an ineffective level of low as an example for illustration. Furthermore, the duty cycle of the PWM signal can be determined according to the control requirements of the actual application scenario, and is not limited here.

[0124] In practical applications, the controller 110 can control some or all of the half-bridge circuits to simultaneously output the bus voltage Vin of the power input terminal VIN, thereby reducing control complexity. However, during transient processes, multiple half-bridge circuits simultaneously outputting the bus voltage Vin of the power input terminal VIN in the magnetically integrated TLVR circuit 120 can cause voltage accumulation in the series-connected secondary winding 22, leading to insulation withstand voltage risks. Therefore, in one embodiment of this application, the first to Mth half-bridge circuits can be divided into at least two drive groups, each drive group including at least two half-bridge circuits. Furthermore, at least one half-bridge circuit must be spaced between any two sequentially appearing half-bridge circuits in any drive group. The controller 110 can sequentially send pulse width modulation (PWM) signals to each drive group; that is, after sending a PWM signal to each half-bridge circuit in one drive group, it then sends a PWM signal to each half-bridge circuit in another drive group, performing cyclic control in sequence. Moreover, the PWM signals sent to each half-bridge circuit in each drive group have a phase difference, allowing the half-bridge circuits in the same drive group to output voltage sequentially without simultaneous output. This control method allows for the use of interleaved PWM signal transmission to balance the number of phases with high-level outputs on both sides of the midpoint of the secondary winding 22 series circuit, thereby reducing the accumulation of secondary voltage.

[0125] For example, taking M=6 as an example, refer to Figure 13 and Figure 14a , Figure 13 This is a schematic diagram of a specific structure of a magnetically integrated TLVR circuit provided in an embodiment of this application. Figure 14a for Figure 13The diagram shows a timing diagram of the PWM signal for the magnetically integrated TLVR circuit. The first half-bridge circuit 121_1 and the fourth half-bridge circuit 121_4 are grouped into a drive group CQ_1, the second half-bridge circuit 121_2 and the fifth half-bridge circuit 121_5 are grouped into a drive group CQ_2, and the third half-bridge circuit 121_1 and the sixth half-bridge circuit 121_6 are grouped into a drive group CQ_3. During operation, the controller 110 first sends a PWM signal SQ_1 to the first half-bridge circuit 121_1, and the PWM signal SQ_1 includes a first PWM signal Sa_1 and a second PWM signal Sb_1. Then, the controller 110 sends a PWM signal SQ_4 to the fourth half-bridge circuit 121_4, and the PWM signal SQ_4 includes a first PWM signal Sa_4 and a second PWM signal Sb_4. Subsequently, controller 110 sends a PWM signal SQ_2 to the second half-bridge circuit 121_2, and the PWM signal SQ_2 includes a first PWM signal Sa_2 and a second PWM signal Sb_2. Then, controller 110 sends a PWM signal SQ_5 to the fifth half-bridge circuit 121_5, and the PWM signal SQ_5 includes a first PWM signal Sa_5 and a second PWM signal Sb_5. Next, controller 110 sends a PWM signal SQ_3 to the third half-bridge circuit 121_3, and the PWM signal SQ_3 includes a first PWM signal Sa_3 and a second PWM signal Sb_3. Finally, controller 110 sends a PWM signal SQ_6 to the sixth half-bridge circuit 121_6, and the PWM signal SQ_6 includes a first PWM signal Sa_6 and a second PWM signal Sb_6.

[0126] In practical applications, the electrical energy output by the magnetically integrated TLVR circuit 120 provided in this embodiment is supplied to the electrical device 12 to power it. However, when the electrical device 12 is working, it may be in a stable energy consumption state for some time periods, and its input current is relatively stable. This indicates that the electrical device 12 is in a steady state. Based on this, the current at the power output terminal VOUT can be collected and compared with a current threshold. If the collected current is less than the current threshold, it indicates that the electrical device 12 is in a steady state and does not require a fast dynamic response. Therefore, in this embodiment, the switching frequency of the PWM signal can be reduced to improve the efficiency of the magnetically integrated TLVR circuit 120. For example, refer to... Figure 14aTaking the first PWM signals Sa_1 and Sa_4 as examples, the high level of the first PWM signal Sa_4 is sent after the high level of the first PWM signal Sa_1 ends, and there is a time interval ta between the falling edge of the high level of the first PWM signal Sa_1 and the rising edge of the high level of the first PWM signal Sa_4. Taking the first PWM signals Sa_1 and Sa_6 as examples, the high level of the first PWM signal Sa_1 is sent after the high level of the first PWM signal Sa_6 ends, and there is a time interval ta between the falling edge of the high level of the first PWM signal Sa_6 and the rising edge of the high level of the first PWM signal Sa_1. With this setting, the frequency of the PWM signals input to the first half-bridge circuit 121_1 to the sixth half-bridge circuit 121_6 can be reduced while reducing the voltage accumulation in the secondary series circuit, thereby reducing losses and improving efficiency. Furthermore, in order to control the uniformity of the PWM signals input to each half-bridge circuit, the controller 110 can control the effective level interval between every two adjacent first PWM signals output sequentially to be the same. Of course, in other embodiments of this application, the interval between the effective levels of adjacent first PWM signals controlled by the controller 110 may be different. It is worth noting that this interval duration ta can be determined according to the needs of the actual application scenario and is not limited here.

[0127] In practical applications, even in steady state, the electrical device 12 may experience sudden loading, leading to increased energy consumption and a sudden increase in input current. This indicates that the electrical device 12 is in a dynamic state. Because the switching frequency of the PWM signal is reduced in steady state to improve efficiency, the reduced frequency results in a poor dynamic response when the device is suddenly loaded. Therefore, in this embodiment, the switching frequency of the PWM signal can be increased to improve the dynamic response capability of the magnetically integrated TLVR circuit 120. Based on this, the sampled current can be compared with a current threshold. If the sampled current is greater than or equal to the current threshold, it indicates that the electrical device 12 is in a dynamic state. The controller 110 can control the effective levels of two adjacent first PWM signals output sequentially to have an overlap duration. Furthermore, to prevent the first switches Qa in the closely spaced half-bridge circuits from conducting simultaneously, the controller 110 also needs to control the effective levels of the first and third sequentially output first PWM signals among the three adjacent first PWM signals to not have an overlap duration. For example, refer to... Figure 14b , Figure 14b for Figure 13Another timing diagram of the PWM signals of the magnetically integrated TLVR circuit 120 is shown. Taking the first PWM signals Sa_1 and Sa_4 as examples, the high level of the first PWM signal Sa_4 can be sent before the high level of the first PWM signal Sa_1 ends, so that the falling edge of the high level of the first PWM signal Sa_1 occurs between the rising edge of the high level of the first PWM signal Sa_4, and there is an overlap duration ta between the high levels of the first PWM signals Sa_1 and Sa_4. Taking the first PWM signals Sa_1 and Sa_6 as examples, the high level of the first PWM signal Sa_1 can be sent before the high level of the first PWM signal Sa_6 ends, so that the falling edge of the high level of the first PWM signal Sa_6 occurs between the rising edge of the high level of the first PWM signal Sa_1, and there is an overlap duration ta between the high levels of the first PWM signals Sa_6 and Sa_1. Furthermore, taking the first PWM signals Sa_1 and Sa_2 as examples, the high level of the first PWM signal Sa_1 ends after the high level of the first PWM signal Sa_2 is sent, and there is a time interval tc between the falling edge of the high level of the first PWM signal Sa_1 and the rising edge of the high level of the first PWM signal Sa_2. This configuration, while reducing the voltage accumulation in the secondary series circuit, can increase the frequency of the PWM signals input to the first half-bridge circuit 121_1 to the sixth half-bridge circuit 121_6, thereby improving dynamic response capability. Further, to control the uniformity of the PWM signals input to each half-bridge circuit, the overlap time between the effective levels of every two adjacent first PWM signals sequentially output by the controller 110 can be made the same. Of course, in other embodiments of this application, the overlap time between the effective levels of some adjacent first PWM signals controlled by the controller 110 can also be made different. Furthermore, the time interval between the effective levels of the first PWM signal output in the first sequence and the third sequence output of three adjacent first PWM signals sequentially output by the controller 110 can be the same, or partially different. It is worth mentioning that the overlap duration tb and the interval duration tc can be determined according to the needs of the actual application scenario, and are not limited here.

[0128] During operation, the output current of the half-bridge circuit and the voltage at the power output terminal VOUT can be kept stable by adjusting the duty cycle of the first PWM signal in the PWM signal. Based on this, in some embodiments of this application, referring to... Figure 13 It can collect the measurement current I of the primary winding 21 of each TLVR inductor 122_1 to 122_M. P_1 ~I P_M And the measured voltage V at the power output terminal VOUT. OThe controller 110 measures the measured current I of the primary winding 21 of any TLVR inductor 122_1 to 122_M. P_1 ~I P_M The measured voltage V at the power output terminal VOUT O This is used to adjust the duty cycle of the PWM signal of the half-bridge circuit corresponding to the TLVR inductor.

[0129] As the switching power supply 100 becomes miniaturized, the material of the magnetic core 23 has gradually changed from ferrite to iron powder core material with high saturation magnetic density. However, the inductance of the iron powder core material exhibits a nonlinear relationship, which brings many difficulties to control. Therefore, in some embodiments of this application, reference is made to... Figure 13 It not only collects the measurement current I of the primary winding 21 of each TLVR inductor 122_1 to 122_M P_1 ~I P_M The measured voltage V at the power output terminal VOUT O It also collects the measurement current I of the secondary winding 22 series circuit. Lc The controller 110 can measure the current I of the primary winding 21 of each TLVR inductor 122_1 to 122_M. P_1 ~I P_M The measured current I of the secondary winding 22 series circuit Lc and the voltage V at the power output terminal VOUT O This is used to adjust the duty cycle of the PWM signal of the half-bridge circuit corresponding to the TLVR inductor, so as to send PWM signals to each half-bridge circuit.

[0130] It is understandable that since the PWM signal received by the half-bridge circuit includes a first PWM signal and a second PWM signal with opposite phases, the aforementioned adjustment of the duty cycle of the PWM signal of the half-bridge circuit refers to adjusting the duty cycle of the first PWM signal of the half-bridge circuit.

[0131] In specific implementation, refer to Figure 15 , Figure 15 This is a flowchart of the control method for the magnetically integrated TLVR circuit in the embodiments of this application. The process of outputting a PWM signal to the half-bridge circuit provided in the embodiments of this application may include the following process:

[0132] S1. During the current testing phase, the measurement current I of the primary winding 21 of each TLVR inductor 122_1 to 122_M is collected. P_1 ~I P_M The measured current I of the secondary winding 22 series circuit Lc and the measured voltage V at the power output terminal VOUT O .

[0133] S2. Based on the measured current I of the secondary winding 22 series circuit. Lc Determine the inductance L of the compensation circuit inductor. Lc .

[0134] S3. Based on the switching states of the first and second PWM signals of each half-bridge circuit 121_1~121_M and the determined inductance L of the compensation circuit inductor... Lc Determine the slope dI of the current in the series circuit of the secondary winding 22. Lc / dt.

[0135] S4. Based on the measured current I of the kth TLVR inductor 122_k among the TLVR inductors 122_1 to 122_M. P_k The measured current I of the series circuit with secondary winding 22 Lc Determine the inductance L of the magnetizing inductor of the k-th TLVR inductor 122_k. m_k .

[0136] S5. Based on the switching states of the first and second PWM signals received by the half-bridge circuit 121_k connected to the k-th TLVR inductor 122_k, and the determined inductance L of the magnetizing inductor 122_k. m_k Determine the slope dI of the current in the magnetizing inductor of the k-th TLVR inductor 122_k. m_k / dt.

[0137] S6. Based on the determined slope dI of the current in the series circuit of the secondary winding 22. Lc The slope dI of the current in the magnetizing inductor of the kth TLVR inductor 122_k is given by / dt. m_k / dt, and the calibration current I of the primary winding 21 of the kth TLVR inductor 122_k determined in the previous detection phase. pk_cali The predicted current I of the primary winding 21 of the k-th TLVR inductor 122_k in the current detection stage is obtained by fitting. pk_fitting .

[0138] S7. Based on the predicted current I of the primary winding 21 of the kth TLVR inductor 122_k obtained by fitting... pk_fitting And the measured current I of the primary winding 21 of the kth TLVR inductor 122_k. P_k Determine the calibration current I of the primary winding 21 of the k-th TLVR inductor 122_k in the current detection phase. pk_cali .

[0139] S8. Based on the calibration current I of the primary winding 21 of the kth TLVR inductor 122_k in the current detection phase. pk_caliAdjust the duty cycle of the first PWM signal corresponding to the half-bridge circuit 121_k connected to the k-th TLVR inductor 122_k, and based on the adjusted duty cycle, output the first PWM signal and the second PWM signal to the half-bridge circuit 121_k connected to the k-th TLVR inductor 122_k.

[0140] It is worth mentioning that steps S2 and S3 can be set before or after steps S4 and S5, or steps S2 and S3 can be performed simultaneously with steps S4 and S5. This application does not limit this.

[0141] Therefore, unlike ordinary buck circuits where the nonlinear inductance is determined solely by the primary winding current, the nonlinear inductance of the magnetically integrated TLVR circuit in this embodiment is determined jointly by the primary and secondary winding currents. In other words, this embodiment simultaneously detects the primary and secondary winding currents and determines the TLVR inductance based on the total current of both windings. This allows for more accurate current prediction and calibration current based on more precise inductance information, thereby improving the control accuracy of the PWM signal and further enhancing the operational stability and reliability of the magnetically integrated TLVR circuit. Furthermore, this embodiment also includes control functions such as current loop and overcurrent protection based on the calibration current.

[0142] In some embodiments of this application, in the magnetically integrated TLVR circuit 120, reference is made to... Figure 2 The compensation circuit inductor can be implemented using a physical inductor element Lc, allowing the compensation circuit inductor and the secondary winding 22 to be set independently and connected by wires. For example, refer to... Figure 2 and Figure 3 The compensation circuit inductor is connected in series between the second end of the secondary winding 22 of TLVR inductor 122_1 and the first end of the secondary winding 22 of TLVR inductor 122_M.

[0143] In other embodiments of this application, in the magnetically integrated TLVR circuit 120, the compensation loop inductor can be integrated into the TLVR inductor by designing at least one leakage inductance of the TLVR inductor, thereby eliminating the physical components of the compensation loop inductor and further reducing the size of the magnetic components in the magnetically integrated TLVR circuit 120. For example, refer to... Figure 16 , Figure 16 This is a schematic diagram of another circuit structure of the magnetically integrated TLVR circuit provided in the embodiments of this application. Figure 16 The magnetically integrated TLVR circuit shown is in Figure 2The magnetically integrated TLVR circuit shown is an improvement upon the previous one. The similarities will not be repeated here; the differences are explained below: Instead of a physical inductor element serving as the compensation loop inductor, leakage inductance L is integrated into each TLVR inductor 122_1 to 122_M. kp_1 ~L kp_M and L ks_1 ~L ks_M This is to form a compensating loop inductance. Understandably, Figure 16 Leakage inductance L kp_1 ~L kp_M and L ks_1 ~L ks_M It is formed by equivalent means.

[0144] Since leakage inductance can generate a negative voltage, the negative voltage generated by the integrated leakage inductance can also offset the voltage of the primary winding 21, thereby reducing the maximum voltage of the series circuit of the secondary winding 22. This reduces the voltage accumulation in the series circuit of the secondary winding 22, which is beneficial for insulation design. Based on this, in some examples of this application, the controller 110 can simultaneously output PWM signals to each half-bridge circuit, that is, the effective levels of the first PWM signals of each half-bridge circuit have partially overlapping durations or fully overlapping durations, thereby simultaneously controlling the output voltage of each half-bridge circuit, thus reducing the control difficulty. For example, refer to Figure 17a and Figure 17b , Figure 17a for Figure 16 A simulated voltage diagram. Figure 17b This is a simulation voltage diagram of the magnetically integrated TLVR circuit in this application embodiment when physical components are used as compensation loop inductors. In the simulation, it is taken as an example that the magnetically integrated TLVR circuit 120 has 12 TLVR inductors 122_1 to 122_12 and simultaneously controls the output voltage of each half-bridge circuit. Furthermore, the simulation process assumes that the voltage at the power input terminal VIN is 12V, the voltage at the power output terminal VOUT is 1V, the inductance of the magnetizing inductor of each TLVR inductor is 100nH, and the leakage inductance L of the TLVR inductors 122_1 to 122_12 is... k_1 ~L k_12 For example, refer to Figure 17a Simulations show that when each half-bridge circuit outputs voltage simultaneously, the maximum voltage in the series circuit of the secondary winding 22 is 36V. (Refer to...) Figure 17b Simulations show that when each half-bridge circuit outputs voltage simultaneously, the maximum voltage in the series circuit of the secondary winding 22 is 132V. Based on this, it can be demonstrated that the voltage accumulation in the series circuit of the secondary winding 22 can be reduced through integrated leakage inductance design. In other examples of this application, it is also possible to... Figure 16 The magnetic integrated TLVR circuit 120 shown adopts Figure 14a and Figure 14bThe signal timing diagram shown is used for control, thereby further reducing the voltage accumulation in the series circuit of the secondary winding 22.

[0145] Exemplarily, an adjustment structure 25 can be integrated into each TLVR inductor to adjust the leakage inductance of the TLVR inductor, thereby making the compensation circuit inductance the leakage inductance of the TLVR inductor with the integrated adjustment structure 25. In some embodiments of this application, reference is made to... Figure 18a and Figure 18b , Figure 18a This is another three-dimensional structural schematic diagram of the magnetically integrated TLVR inductor provided in the embodiments of this application. Figure 18b for Figure 18a The cross-sectional view along the AA' direction, taking TLVR inductors 122_1 to 122_2 as examples, shows that TLVR inductors 122_1 to 122_2 integrate an adjustment structure 25. The adjustment structure 25 is filled in the gaps between the bending areas of the first pin P1 and the first U-shaped structure U1, and between the bending areas of the third pin P3 and the second U-shaped structure U2. Similarly, the adjustment structure 25 can be filled in the gaps between the bending areas of the second pin P2 and the first U-shaped structure U1, and between the fourth pin P4 and the second U-shaped structure U2. Alternatively, the adjustment structure 25 can be filled in the bending areas of some or all of the TLVR inductors, specifically between the first pin P1 and the first U-shaped structure U1, and between the third pin P3 and the second U-shaped structure U2. It is worth mentioning that by filling these gaps with adjustment structures 25, the volume of the magnetic core 23 or the area of ​​the winding is not sacrificed.

[0146] For example, the adjustment structure 25 may include: a magnetic core 23 material and an insulating material layer disposed between the magnetic core 23 material and the primary winding 21 and the secondary winding 22. This configuration allows the magnetic core 23 material covered by the insulating material layer to fill the aforementioned gaps, reducing the difficulty of material selection and facilitating the formation of a single-piece structure for the magnetically integrated TLVR inductor.

[0147] It is worth mentioning that other methods can also be used to form the adjustment structure to adjust the leakage inductance of the TLVR inductor, and this application does not limit this.

[0148] In some embodiments of this application, several half-bridge circuits close to the middle sequence can be selected from the sequentially appearing first to Mth half-bridge circuits. The first or second terminal of the secondary winding 22 corresponding to these half-bridge circuits is connected to the ground terminal GND. This is equivalent to grounding the secondary winding 22 series circuit near the negative position of the corresponding middle sequence half-bridge circuit, thereby dividing the voltage of the secondary winding 22 series circuit into positive and negative intervals. The voltage can be reduced to a maximum of half the original maximum voltage of the secondary winding 22 series circuit, effectively reducing voltage accumulation in the secondary winding 22 series circuit and benefiting insulation design. Based on this, in some examples of this application, the controller 110 can simultaneously output PWM signals to each half-bridge circuit, i.e., the effective levels of the first PWM signals of each half-bridge circuit have partially or completely overlapping durations, thereby simultaneously controlling the output voltage of each half-bridge circuit and reducing control difficulty. In other examples of this application, the magnetically integrated TLVR circuit 120 can also adopt... Figure 14a and Figure 14b The signal timing diagram shown is used for control, thereby further reducing the voltage accumulation in the series circuit of the secondary winding 22.

[0149] In some examples, M can be an even number, for example, Figure 19 This is a schematic diagram of another circuit structure of the magnetically integrated TLVR circuit provided in the embodiments of this application. Figure 19 The magnetically integrated TLVR circuit shown is in Figure 2 The magnetically integrated TLVR circuit shown is an improvement upon the previous one. The similarities will not be repeated here; the differences are explained below: Taking M=12 as an example, the first end of the secondary winding 22 of the TLVR inductor 122_6 connected to the 6th half-bridge circuit 121_6 and the second end of the secondary winding 22 of the TLVR inductor 122_7 connected to the 7th half-bridge circuit 121_7 can be connected to the ground terminal GND. This configuration effectively halves the maximum voltage of the series circuit of the secondary winding 22. Alternatively, the first end of the secondary winding 22 of the TLVR inductor 122_5 connected to the 5th half-bridge circuit 121_5 and the second end of the secondary winding 22 of the TLVR inductor 122_6 connected to the 6th half-bridge circuit 121_6 can also be connected to the ground terminal GND. Alternatively, the first end of the secondary winding 22 of the TLVR inductor 122_7 connected to the 7th half-bridge circuit 121_7 and the second end of the secondary winding 22 of the TLVR inductor 122_8 connected to the 8th half-bridge circuit 121_8 can be connected to the ground terminal GND.

[0150] For example, refer to Figure 20 , Figure 20 for Figure 19A simulated voltage diagram is provided. In the simulation, a magnetically integrated TLVR circuit 120 with 12 TLVR inductors 122_1 to 122_12 is used as an example, simultaneously controlling the output voltage of each half-bridge circuit. Furthermore, the simulation process assumes a power input voltage of 12V at VIN, a power output voltage of 1V at VOUT, a magnetizing inductance of 100nH for each TLVR inductor, and a leakage inductance L in the TLVR inductors 122_1 to 122_12. k_1 ~L k_12 For example, refer to Figure 20 When each half-bridge circuit outputs voltage simultaneously, simulation shows that the voltage in the secondary winding 22 series circuit is generally negative and generally positive, thus dividing the voltage of the secondary winding 22 series circuit into two intervals, effectively halving the highest voltage of the secondary winding 22 series circuit, thereby reducing the voltage accumulation of the secondary winding 22 series circuit.

[0151] In other examples, M can also be an odd number, for example, Figure 21 This is a schematic diagram of another circuit structure of the magnetically integrated TLVR circuit provided in the embodiments of this application. Figure 21 The magnetically integrated TLVR circuit shown is in Figure 2 The magnetically integrated TLVR circuit shown is an improvement upon the previous one. The similarities will not be repeated here; the differences are explained below: Taking M=13 as an example, the first end of the secondary winding 22 of the TLVR inductor 122_7 connected to the 7th half-bridge circuit 121_7 and the second end of the secondary winding 22 of the TLVR inductor 122_8 connected to the 8th half-bridge circuit 121_8 can be connected to the ground terminal GND. This configuration effectively reduces the maximum voltage of the series circuit of the secondary winding 22. Alternatively, the first end of the secondary winding 22 of the TLVR inductor 122_6 connected to the 6th half-bridge circuit 121_6 and the second end of the secondary winding 22 of the TLVR inductor 122_7 connected to the 7th half-bridge circuit 121_7 can also be connected to the ground terminal GND. Alternatively, the first end of the secondary winding 22 of the TLVR inductor 122_8 connected to the 8th half-bridge circuit 121_8 and the second end of the secondary winding 22 of the TLVR inductor 122_9 connected to the 9th half-bridge circuit 121_9 can be connected to the ground terminal GND.

[0152] It is worth mentioning that various implementations of the magnetically integrated TLVR inductor in the embodiments of this application may not depend on the magnetically integrated TLVR circuit in this application, and may be other implementable methods, which are not limited here.

[0153] Based on this, the present application also provides a control method for controlling the magnetically integrated TLVR circuit in the present application; wherein, each half-bridge circuit includes a first switch and a second switch connected in series between the power input terminal and the ground terminal, and the control terminal of each first switch and the control terminal of the second switch are used to connect to a controller; the multiple half-bridge circuits include a first half-bridge circuit to an Mth half-bridge circuit arranged in sequence, the first half-bridge circuit to the Mth half-bridge circuit are divided into at least two drive groups, each drive group includes at least two half-bridge circuits, and at least one half-bridge circuit is spaced between two half-bridge circuits that appear in sequence in any drive group.

[0154] Furthermore, the control method includes: sequentially sending pulse width modulation (PWM) signals to each of at least two drive groups, and the PWM signals sent to each half-bridge circuit in each drive group sequentially having a phase difference; wherein the PWM signals include a first PWM signal and a second PWM signal, the first PWM signal is used to input the control terminal of the first switch, the second PWM signal is used to input the control terminal of the second switch, and the phases of the first PWM signal and the second PWM signal received by any half-bridge circuit are opposite.

[0155] In some embodiments, PWM signals are sent to each half-bridge circuit based on the measured current of each primary winding, the measured current of the series circuit, and the measured voltage at the power output terminal.

[0156] In some embodiments, PWM signals are sent to each half-bridge circuit based on the measured current of each primary winding, the measured current of the series circuit, and the measured voltage at the power supply output terminal, including:

[0157] In the current detection phase, the predicted current of the primary winding of each TLVR inductor is obtained by fitting the measured current of each primary winding, the measured current of the series circuit, the measured voltage of the power supply output terminal, and the switching state of the PWM signal received by each half-bridge circuit.

[0158] The calibration current of the primary winding of each TLVR inductor is determined based on the predicted current and the measured current of the primary winding of each TLVR inductor.

[0159] Based on the calibration current of the primary winding of each TLVR inductor, the duty cycle of the first PWM signal of the half-bridge circuit connected to each TLVR inductor is adjusted, and based on the adjusted duty cycle, the first PWM signal and the second PWM signal are output to the corresponding half-bridge circuit.

[0160] In some embodiments, fitting the predicted current of the primary winding of each TLVR inductor includes:

[0161] The slope of the current in the series circuit is determined based on the measured current of the series circuit and the switching states of the first and second PWM signals of each half-bridge circuit.

[0162] The slope of the current of the magnetizing inductor of the kth TLVR inductor is determined based on the measured current of the primary winding of the kth TLVR inductor, the measured current of the series circuit, and the switching states of the first PWM signal and the second PWM signal received by the half-bridge circuit connected to the kth TLVR inductor.

[0163] Based on the slope of the current in the determined series circuit, the slope of the current in the magnetizing inductance of the kth TLVR inductor, and the calibration current of the primary winding of the kth TLVR inductor determined in the previous detection stage, the predicted current of the primary winding of the kth TLVR inductor in the current detection stage is obtained by fitting.

[0164] In some embodiments, determining the slope of the current in the series loop based on the measured current of the series loop and the switching states of the first PWM signal and the second PWM signal of each half-bridge circuit includes:

[0165] Determine the inductance of the compensation circuit based on the measured current of the series circuit;

[0166] The slope of the current in the series circuit is determined based on the switching states of the first and second PWM signals received by each half-bridge circuit and the inductance of the compensation circuit inductor.

[0167] In some embodiments, determining the slope of the current in the magnetizing inductor of the kth TLVR inductor based on the measured current of the primary winding of the kth TLVR inductor, the measured current of the series circuit, and the switching states of the first PWM signal and the second PWM signal received by the half-bridge circuit connected to the kth TLVR inductor includes:

[0168] Determine the inductance of the magnetizing inductor of the kth TLVR based on the measured current of the kth TLVR inductor and the measured current of the series circuit.

[0169] Based on the switching states of the first and second PWM signals received by the half-bridge circuit connected to the k-th TLVR inductor and the determined inductance of the magnetizing inductor of the k-th TLVR inductor, the slope of the current of the magnetizing inductor of the k-th TLVR inductor is determined.

[0170] In some embodiments, the control method further includes: in response to the current at the power supply output terminal being greater than or equal to a current threshold, controlling the effective levels of two adjacent first PWM signals output sequentially to have an overlap duration, and controlling the effective levels of the first PWM signal output in the first sequence and the first PWM signal output in the third sequence among the three adjacent first PWM signals output sequentially to not have an overlap duration.

[0171] In some embodiments, the control method further includes: in response to the current at the power supply output terminal being less than a current threshold, controlling the effective levels of two adjacent first PWM signals output sequentially to have an interval duration.

[0172] The above description is only a specific implementation of this application, but the protection scope of this application is not limited thereto. Any changes or substitutions that can be easily conceived by those skilled in the art within the scope of the technology disclosed in this application should be included within the protection scope of this application.

Claims

1. A magnetic integrated TLVR circuit, characterized by, The application relates to a TLVR inductor and a TLVR inductor circuit. The TLVR inductor comprises a plurality of half-bridge circuits and a plurality of TLVR inductors. The plurality of TLVR inductors correspond to the plurality of half-bridge circuits one by one, the first end of any half-bridge circuit is connected with a power input end, the second end of any half-bridge circuit is connected with a ground end, the switch node of any half-bridge circuit is connected with the first end of the primary winding of the corresponding TLVR inductor, the second end of the primary winding of any TLVR inductor is connected with a power output end, the secondary windings of the plurality of TLVR inductors are connected in series with a compensation loop inductor to form a series loop, and the series loop is connected to the ground end. The plurality of half-bridge circuits comprise a first half-bridge circuit to an Mth half-bridge circuit arranged in sequence, the first half-bridge circuit to the Mth half-bridge circuit are divided into at least one circuit group, the circuit group comprises at least two half-bridge circuits arranged in sequence, the TLVR inductors connected with each half-bridge circuit in any circuit group share a magnetic core to be integrated into one magnetic integrated TLVR inductor, and in any magnetic integrated TLVR inductor, the mutual inductance coupling coefficient of each primary winding is greater than zero, and the winding direction of the first end to the second end of each primary winding is the same as the winding direction of the first end to the second end of each secondary winding.

2. The magnetic integrated TLVR circuit of claim 1, wherein, In any TLVR inductor, the secondary winding is wound on the magnetic core, the primary winding is wound on the secondary winding, and an insulation layer is arranged between the primary winding and the secondary winding to form a nested structure. The nested structures in any magnetic integrated TLVR inductor are arranged in sequence and spaced apart along the extension direction of the magnetic core.

3. The magnetic integrated TLVR circuit of claim 2, wherein, The primary winding has a first U-shaped structure in a sheet shape, the secondary winding has a second U-shaped structure in a sheet shape, the second U-shaped structure is arranged in a containing cavity of the first U-shaped structure, and the opening direction of the second U-shaped structure and the first U-shaped structure is the same.

4. The magnetic integrated TLVR circuit of claim 3, wherein, The primary winding further has a first pin in a sheet shape and a second pin in a sheet shape, the first pin is connected to one end of the first U-shaped structure and extends outward, and the second pin is connected to the other end of the first U-shaped structure and extends outward. The secondary winding further has a third pin in a sheet shape and a fourth pin in a sheet shape, the third pin is connected to one end of the second U-shaped structure and extends inward, and the fourth pin is connected to the other end of the second U-shaped structure and extends inward. In any TLVR inductor, the first pin and the third pin are spaced apart as the first end, and the second pin and the fourth pin are spaced apart as the second end.

5. The magnetic integrated TLVR circuit of claim 3 or 4, wherein, In any magnetic integrated TLVR inductor, the primary winding and the secondary winding are embedded in the magnetic core, or any magnetic integrated TLVR inductor is an integrally formed structure.

6. The magnetic integrated TLVR circuit of claim 5, wherein, In at least one magnetic integrated TLVR inductor, the upper surface of the side, away from the opening, of each first U-shaped structure is exposed outside the magnetic core.

7. The magnetic integrated TLVR circuit of claim 5 or 6, wherein, In at least one magnetic integrated TLVR inductor, the magnetic core is protrudingly arranged away from the opening side of each first U-shaped structure.

8. The magnetic integrated TLVR circuit of any one of claims 1-7, wherein, At least one of the TLVR inductors is integrated with an adjusting structure for adjusting leakage inductance of the TLVR inductor; the compensation loop inductor is leakage inductance of the TLVR inductor integrated with the adjusting structure.

9. The magnetic integrated TLVR circuit of any of claims 4-8, wherein, The adjusting structure is filled between the bending area between the first pin and the first U-shaped structure and the bending area between the third pin and the second U-shaped structure, or the adjusting structure is filled between the bending area between the second pin and the first U-shaped structure and the bending area between the fourth pin and the second U-shaped structure. The adjusting structure comprises a magnetic core material and an insulating material layer arranged between the magnetic core material and the primary winding and the secondary winding.

10. The magnetic integrated TLVR circuit of any one of claims 1-7, wherein, The compensation loop inductor is independently arranged with the secondary winding and is connected through a wire.

11. The magnetic integrated TLVR circuit of any one of claims 1-10, wherein, Each of the half-bridge circuits comprises a first switch and a second switch connected in series between the power input end and the ground end, and a control end of each of the first switches and a control end of each of the second switches are used for connecting a controller; The first half-bridge circuit to the Mth half-bridge circuit are divided into at least two driving groups, each of the driving groups comprises at least two half-bridge circuits, and at least one half-bridge circuit is arranged between two half-bridge circuits sequentially arranged in any of the driving groups; The controller is used for: sequentially sending a pulse width modulation (PWM) signal to each of the at least two driving groups, and the PWM signals sent to each of the half-bridge circuits in each of the driving groups sequentially have a phase difference; wherein the PWM signal comprises a first PWM signal and a second PWM signal, the first PWM signal is used for inputting the control end of the first switch, the second PWM signal is used for inputting the control end of the second switch, and the phases of the first PWM signal and the second PWM signal received by any of the half-bridge circuits are opposite.

12. The magnetic integrated TLVR circuit of claim 11, wherein, The controller is further used for: in response to the current of the power output end being less than a current threshold, controlling a time length of interval between effective levels of two adjacent first PWM signals output sequentially.

13. The magnetic integrated TLVR circuit of claim 11 or 12, wherein, The controller is further used for: in response to the current of the power output end being greater than or equal to the current threshold, controlling a time length of overlap between effective levels of two adjacent first PWM signals output sequentially, and controlling that effective levels of a first first PWM signal output first and a third first PWM signal output third in three first PWM signals output sequentially do not have a time length of overlap.

14. The magnetic integrated TLVR circuit of any of claims 11-13, wherein, The controller is further used for: sending the PWM signal to each of the half-bridge circuits according to a measured current of each of the primary windings, a measured current of the series circuit and a measured voltage of the power output end.

15. The magnetic integrated TLVR circuit of any one of claims 1-10, wherein, The plurality of half-bridge circuits is even, a first end of a secondary winding of a TLVR inductor connected with an M / 2th half-bridge circuit or a first end of a secondary winding of a TLVR inductor connected with a half-bridge circuit sequentially adjacent to the M / 2th half-bridge circuit is connected to the ground end. Alternatively, the plurality of half-bridge circuits is odd, a first end of a secondary winding of a TLVR inductor connected to an (M+1) / 2th half-bridge circuit or a first end of a secondary winding of a TLVR inductor connected to a half-bridge circuit adjacent to the (M+1) / 2th half-bridge circuit is connected to the ground terminal.

16. A control method characterized by, The control method is used for controlling the magnetic integrated TLVR circuit according to any one of claims 1-15; each of the half-bridge circuits comprises a first switch and a second switch connected in series between the power input terminal and the ground terminal, a control terminal of each of the first switches and a control terminal of each of the second switches are used for connecting a controller; the plurality of half-bridge circuits comprises a first half-bridge circuit to an Mth half-bridge circuit arranged in sequence, the first half-bridge circuit to the Mth half-bridge circuit are divided into at least two driving groups, each of the driving groups comprises at least two half-bridge circuits, and at least one half-bridge circuit is arranged between two half-bridge circuits arranged in sequence in any one of the driving groups; The control method comprises: sending a pulse width modulation (PWM) signal to each of the at least two driving groups in sequence, and the PWM signals sent to each of the half-bridge circuits in each of the driving groups have a phase difference in sequence; wherein the PWM signal comprises a first PWM signal and a second PWM signal, the first PWM signal is used for inputting the control terminal of the first switch, and the second PWM signal is used for inputting the control terminal of the second switch, and the phase of the first PWM signal and the second PWM signal received by any one of the half-bridge circuits is opposite.

17. The control method of claim 16, wherein The PWM signal is sent to each of the half-bridge circuits according to the measured current of each of the primary windings, the measured current of the series circuit and the measured voltage of the power output terminal.

18. The control method according to claim 17, characterized by, The PWM signal is sent to each of the half-bridge circuits according to the measured current of each of the primary windings, the measured current of the series circuit and the measured voltage of the power output terminal, comprising: in the current detection stage, a predicted current of the primary winding of each of the TLVR inductors is fitted according to the measured current of each of the primary windings, the measured current of the series circuit, the measured voltage of the power output terminal and the switching state of the PWM signal received by each of the half-bridge circuits; a calibration current of the primary winding of each of the TLVR inductors is determined according to the predicted current and the measured current of the primary winding of each of the TLVR inductors; a duty cycle of the first PWM signal of the half-bridge circuit connected to each of the TLVR inductors is adjusted according to the calibration current of the primary winding of each of the TLVR inductors, and the first PWM signal and the second PWM signal are output to the corresponding half-bridge circuit according to the adjusted duty cycle.

19. The control method according to claim 18, characterized by, The predicted current of the primary winding of each of the TLVR inductors is fitted, comprising: a slope of the current of the series circuit is determined according to the measured current of the series circuit and the switching state of the first PWM signal and the second PWM signal of each of the half-bridge circuits; determine a slope of the current of the excitation inductance of the kth TLVR inductor according to the measured current of the primary winding of the kth TLVR inductor, the measured current of the series loop, and the switching states of the first PWM signal and the second PWM signal received by the half-bridge circuit connected to the kth TLVR inductor; fit a predicted current of the primary winding of the kth TLVR inductor in the current detection stage according to the determined slope of the current of the series loop, the determined slope of the current of the excitation inductance of the kth TLVR inductor, and the calibrated current of the primary winding of the kth TLVR inductor determined in the last detection stage.

20. The control method of claim 19, wherein The method further comprises: determine the inductance of the compensation loop inductor according to the measured current of the series loop; determine the slope of the current of the series loop according to the measured current of the series loop and the switching states of the first PWM signal and the second PWM signal received by each half-bridge circuit.

21. The control method according to claim 19 or 20, characterized by, The method further comprises: determine the inductance of the compensation loop inductor according to the measured current of the series loop; determine the slope of the current of the series loop according to the measured current of the series loop and the switching states of the first PWM signal and the second PWM signal received by each half-bridge circuit.

22. A control method according to any one of claims 16 to 21, characterized in that, The method further comprises: determine the inductance of the excitation inductance of the kth TLVR inductor according to the measured current of the kth TLVR inductor and the measured current of the series loop; 23. A control method according to any one of claims 16 to 22, characterised by, determine the slope of the current of the excitation inductance of the kth TLVR inductor according to the switching states of the first PWM signal and the second PWM signal received by the half-bridge circuit connected to the kth TLVR inductor and the determined inductance of the excitation inductance of the kth TLVR inductor. The method further comprises:

24. A switched mode power supply characterized by in response to the current of the power output end being less than the current threshold, control the adjacent two first PWM signals in the sequential output to have a time length of interval between the active levels. The method further comprises:

25. An electronic device, comprising: in response to the current of the power output end being greater than or equal to the current threshold, control the adjacent two first PWM signals in the sequential output to have a time length of overlap between the active levels, and control the active levels of the first first PWM signal in the first sequential output and the third first PWM signal in the third sequential output among the adjacent three first PWM signals in the sequential output to have no time length of overlap. The control method comprises: the controller is connected to each half-bridge circuit in the magnetic integrated TLVR circuit, and is configured to output PWM signals to each half-bridge circuit to control the operation of each half-bridge circuit. The switching power supply comprises a power utilization device and the switching power supply of claim 24, and the output end of the switching power supply is connected to the power utilization device.

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