Transmitting reflecting elements of an antenna and a transreflective array antenna

Abstract

The application relates to the technical field of wireless communication, and discloses a transmission-reflection unit of an antenna and a transmission-reflection array antenna, the unit comprising a reflection patch, a first substrate, a first grid layer, a second substrate, a transmission patch, a third substrate and a second grid layer arranged in sequence; the reflection patch comprises a first W-shaped patch and C-shaped patches symmetrically arranged on both sides of the middle part of the first W-shaped patch; the first grid layer and the second grid layer are a plurality of metal strips arranged in an orthogonal mode; the transmission patch comprises a second W-shaped patch, a square patch and two rectangular patches, the two ends of the second W-shaped patch are arc-shaped patches, the length direction of the second W-shaped patch and the length direction of the first grid layer form an included angle of 45 degrees, the square patch is arranged in the middle of the second W-shaped patch, and the two rectangular patches are symmetrically arranged on both sides of the square patch. The size parameters of the reflection patch and the transmission patch can be adjusted to adjust the reflection phase shift value and the transmission phase shift value of the unit, and the array antenna composed of the unit has the characteristics of wide bandwidth, high gain and multiple modes.

Description

Technical Field

[0001] This invention relates to the field of wireless communication technology, specifically to a transmission and reflection element and a transmission and reflection array antenna for an antenna. Background Technology

[0002] In the context of non-line-of-sight (NLOS) propagation applications, transmission-reflection array antennas, as a high-gain antenna, offer significant advantages. They eliminate the need for complex feeding networks, thus avoiding transmission losses and making them particularly suitable for millimeter-wave and terahertz communication bands. Compared to transmission or reflection arrays that radiate only from one side, transmission-reflection array antennas can radiate from both sides of space, better meeting multi-angle communication requirements, which is especially important for NLOS propagation in complex environments.

[0003] With the increasing demand for faster data rates, future 5G / 6G communication systems place higher demands on wider operating bandwidth and greater communication capacity. Wideband array antennas need to possess a wide 1-dB or 3-dB gain bandwidth to meet these requirements. However, while researchers have implemented wideband elements using multi-resonator structures, delay line units, and through-hole structures, most of these designs have relatively low gain, failing to meet the demands of long-distance, high-speed data transmission. Furthermore, there is still room for further improvement in gain bandwidth to accommodate the future communication system's requirements for wider operating bandwidth and greater capacity. Summary of the Invention

[0004] One of the objectives of this invention is to provide a transmission and reflection unit for an antenna that has good reflection and transmission performance, and can generate a phase shift value within a preset range by changing its own structural parameters.

[0005] Another objective of this invention is to provide a transmissive-reflective array antenna comprising an M×N array of several transmissive-reflective elements, which has wide bandwidth, high gain, and multi-mode characteristics, thereby improving the performance of communication systems and enabling more efficient signal transmission in complex NLOS propagation environments.

[0006] To achieve the above objectives, the present invention provides a transmission and reflection unit for an antenna, comprising a reflective patch, a first substrate, a first grating layer, a second substrate, a transmission patch, a third substrate, and a second grating layer arranged sequentially; the reflective patch includes a first I-shaped patch and two C-shaped patches symmetrically arranged on both sides of the middle portion of the first I-shaped patch, the bottom of the C-shaped patches being parallel to the central branch of the first I-shaped patch, and the opening of the C-shaped patches facing away from the first I-shaped patch; adjusting the bottom length of the C-shaped patches can adjust the phase shift value generated by the transmission and reflection unit when reflecting X-polarized signals; the first grating layer is parallel to the length direction of the first I-shaped patch. The first gate layer consists of several metal strips, and the second gate layer consists of several metal strips perpendicular to the first gate layer. The transmission patch includes a second I-shaped patch, a square patch, and two rectangular patches connected in sequence. The two ends of the second I-shaped patch are arc-shaped pieces with openings facing each other. The length direction of the second I-shaped patch forms a 45° angle with the length direction of the first gate layer. The square patch is centrally and vertically disposed in the middle of the second I-shaped patch. The two rectangular patches are centrally disposed on both sides of the square patch. Adjusting the length of the rectangular patches and the setting angle of the transmission patches can adjust the phase shift value generated by the transmission and reflection unit when transmitting Y-polarized signals.

[0007] As one implementation, the phase shift value generated by the transmission and reflection unit when reflecting the X-polarized signal Length of the bottom of the C-shaped patch The relationship is: .

[0008] As one implementation, the phase shift value generated by the transmission and reflection unit when transmitting a Y-polarized signal and , and The relationship is:

[0009] hour, ;

[0010] hour, ;

[0011] , ;

[0012] In the formula, S As an intermediate parameter, The length of the rectangular patch. To set the angle for the transmissive patch. The angle is the angle between the center and end of the arc-shaped piece and the center of the second I-shaped patch, respectively.

[0013] In one embodiment, an air layer is provided between the first substrate and the second substrate.

[0014] To achieve the above objectives, the present invention provides a transmissive-reflective array antenna, comprising: M×N transmissive-reflective elements as described above, where M and N are natural numbers not less than 1, and M×N is not less than 2; and a feed source disposed on the side of the transmissive-reflective elements near the reflective patch.

[0015] In one embodiment, the thickness of the air layer in the transmission and reflection unit is 0.6 mm.

[0016] In one implementation, M×N is 25×25, the array size is 100mm×100mm×2.214mm, and the focal diameter ratio F / D=1.

[0017] In one embodiment, the width of the metal strip is 1.01 mm, the spacing between the metal strips is 0.32 mm, the width of each branch in the first I-shaped patch and the width of the two sides of the C-shaped patch are both 0.2 mm, the bottom width of the C-shaped patch is 0.3 mm, the width of each branch in the second I-shaped patch and the width of the rectangular patch are both 0.3 mm, the width direction of the rectangular patch is parallel to the length direction of the second I-shaped patch, and the side length of the square patch is 1.4 mm.

[0018] In one implementation, the transmissive-reflective array antenna is configured to output a pencil-shaped beam, and the phase compensation value required by each of the transmissive-reflective elements is... for:

[0019]

[0020] In the formula, The positions of each of the aforementioned transmission and reflection units. The location of the feed source, The direction of the pencil-shaped beam. The wavelength of the radiated electromagnetic wave is denoted as λ.

[0021] As one implementation, the transmissive-reflective array antenna is configured to output an OAM vortex beam, and the phase compensation value required by each of the transmissive-reflective elements is... for:

[0022]

[0023] In the formula, The positions of each of the aforementioned transmission and reflection units. The location of the feed source, The direction of the OAM vortex beam. lIn OAM mode, under transmission state l =+1, in the reflection state l =-1, The wavelength of the radiated electromagnetic wave is denoted as λ.

[0024] Based on the above description and practice, it can be seen that in the transmission and reflection unit of the antenna described in this invention, the first and second grating layers are mutually orthogonal metal strips. On the one hand, they separate the incident waves polarized along the X-axis and Y-axis, giving the unit polarization selectivity. On the other hand, their orthogonal placement creates a Fabry cavity effect, which enhances the transmission amplitude of the unit. The transmission patch consists of a second I-shaped patch placed at a 45-degree angle, a retractable rectangular patch perpendicular to it, and a square patch. By adjusting the length of the rectangular patch and the setting angle of the transmission patch, the phase shift value generated by the transmission and reflection unit when transmitting Y-polarized signals can be adjusted, resulting in good transmission phase and amplitude response. The reflection patch consists of a first I-shaped patch and a pair of mirror-symmetrical C-shaped patches. By adjusting the bottom length of the C-shaped patch, the phase shift value generated by the transmission and reflection unit when reflecting X-polarized signals can be adjusted, resulting in good reflection phase and amplitude response. The transmission and reflection unit of this antenna has good reflection and transmission performance, and can generate a phase shift value within a preset range by changing its own structural parameters.

[0025] The transmissive-reflective array antenna of the present invention uses the above-mentioned transmissive-reflective elements to form an array. The entire antenna has wide bandwidth, high gain, and multi-mode characteristics, which can improve the performance of the communication system and achieve more efficient signal transmission in complex NLOS propagation environments. Attached Figure Description

[0026] Figure 1 This is a schematic diagram of the transmission and reflection unit of an antenna according to one embodiment of the present invention, wherein the left side is the structure in the assembled state and the right side is the structure in the disassembled state.

[0027] Figure 2 and Figure 3 This is a schematic diagram of the structure of the transmission patch in the transmission and reflection unit of an antenna according to one embodiment of the present invention.

[0028] Figure 4 This is a schematic diagram of the structure of the reflective patch in the transmission and reflection unit of an antenna according to one embodiment of the present invention.

[0029] Figure 5 This is a schematic diagram illustrating the polarization separation effect of two gate layers in a transmission and reflection unit according to one embodiment of the present invention.

[0030] Figure 6 This is a schematic diagram illustrating the influence of the two grating layers of the transmission and reflection unit on the transmission amplitude in one embodiment of the present invention.

[0031] Figure 7 This is a schematic diagram illustrating the effect of the air layer of the transmission and reflection unit on the reflection phase in one embodiment of the present invention.

[0032] Figures 8a-8c The figures shown are current distribution diagrams of the transmission patch of the transmission and reflection unit involved in one embodiment of the present invention at 22GHz, 26GHz, and 32GHz.

[0033] Figures 9a-9c The figures shown are current distribution diagrams of the reflective patch of the transmission and reflection unit involved in one embodiment of the present invention at 22GHz, 26GHz, and 32GHz.

[0034] Figure 10a This is a schematic diagram illustrating the relationship between the transmission phase and parameter S in a transmission and reflection unit according to one embodiment of the present invention.

[0035] Figure 10b This is a schematic diagram illustrating the relationship between the transmission amplitude and parameter S in a transmission and reflection unit according to one embodiment of the present invention.

[0036] Figure 10c In one embodiment of the present invention, the transmission phase and the transmission reflection unit are involved. A diagram illustrating the relationship between the two.

[0037] Figure 10d In one embodiment of the present invention, the transmission amplitude in the transmission and reflection unit is related to... A diagram illustrating the relationship between the two.

[0038] Figure 11a In one embodiment of the present invention, the reflection phase in the transmission and reflection unit is related to... A diagram illustrating the relationship between the two.

[0039] Figure 11b In one embodiment of the present invention, the reflection amplitude in the transmission and reflection unit is related to... A diagram illustrating the relationship between the two.

[0040] Figure 12 This is a schematic diagram illustrating the working principle of a transmissive and reflective array antenna according to one embodiment of the present invention.

[0041] Figure 13 This is an exploded view of a transflective array antenna according to one embodiment of the present invention, in which the feed source is not shown.

[0042] Figure 14 This is a schematic diagram of the structure of a transmission array composed of multiple transmission patches in a transmission-reflection array antenna according to one embodiment of the present invention.

[0043] Figure 15 This is a schematic diagram of the structure of a reflective array composed of multiple reflective patches in a transflective array antenna according to one embodiment of the present invention.

[0044] Figure 16 This is a phase compensation diagram of each transmission patch of the transmissive-reflective array antenna in one embodiment of the present invention when it outputs a pencil-shaped beam.

[0045] Figure 17 This is a phase compensation diagram of each reflective patch of the transflective array antenna in one embodiment of the present invention when it outputs a pencil-shaped beam.

[0046] Figure 18 This is a simulation result from HFSS simulation of a transflective array antenna in one embodiment of the present invention when it outputs a pencil-shaped beam.

[0047] Figure 19 This is a schematic diagram showing the gain of a transflective array antenna in one embodiment of the present invention when outputting a pencil-shaped beam.

[0048] Figures 20a to 20c The normalized 2D radiation patterns of the transmitted beam of the transmissive-reflective array antenna involved in one embodiment of the present invention at 22 GHz, 26 GHz and 30 GHz.

[0049] Figures 21a to 21c This is a normalized 2D radiation pattern of the reflected beam of the transflective array antenna involved in one embodiment of the present invention at 22 GHz, 26 GHz and 30 GHz.

[0050] Figure 22 This is a phase compensation diagram of each transmission patch of the transmissive-reflective array antenna in one embodiment of the present invention when outputting an OAM vortex beam.

[0051] Figure 23 This is a phase compensation diagram of each reflective patch of the transflective array antenna in one embodiment of the present invention when outputting an OAM vortex beam.

[0052] Figure 24 This is a schematic diagram of the structure of the transmission and reflection array antenna in one embodiment of the present invention when outputting an OAM vortex beam.

[0053] Figure 25 This is a schematic diagram of the structure of the reflective array of the transflective array antenna in one embodiment of the present invention when outputting an OAM vortex beam.

[0054] Figure 26 In one embodiment of the present invention, the transmissive and reflective array antenna is in the transmission state. lIn the +1 mode, the 3D radiation pattern, near-field amplitude and phase distribution of the OAM vortex beam at 22GHz, 26GHz and 30GHz.

[0055] Figure 27 This is a mode purity diagram of the transmitted beam of a transmissive-reflective array antenna at a frequency of 26 GHz, according to one embodiment of the present invention.

[0056] Figure 28 In one embodiment of the present invention, the transmissive-reflective array antenna is in a reflection state. l In the -1 mode, the 3D radiation pattern, near-field amplitude and phase distribution of the OAM vortex beam at 22GHz, 26GHz and 30GHz.

[0057] Figure 29 This is a mode purity diagram of the reflected beam of a transflective array antenna at a frequency of 26 GHz, according to one embodiment of the present invention. Detailed Implementation

[0058] Exemplary embodiments will now be described more fully with reference to the accompanying drawings. However, exemplary embodiments can be implemented in many forms and should not be construed as limited to the examples set forth herein; rather, these embodiments are provided so that this disclosure will be more comprehensive and complete, and will fully convey the concept of exemplary embodiments to those skilled in the art. The described features, structures, or characteristics may be combined in any suitable manner in one or more embodiments.

[0059] Furthermore, the accompanying drawings are merely illustrative of this disclosure and are not necessarily drawn to scale. The same reference numerals in the drawings denote the same or similar parts, and therefore repeated descriptions of them will be omitted. It should be noted that in this disclosure, the terms "comprising," "configured with," and "set in" are used to indicate an open-ended inclusion, meaning that additional elements / components / etc. may exist besides those listed; the terms "first," "second," etc., are used only as labels and are not intended to limit the number or order of objects; the terms "center," "upper," "lower," "left," "right," "vertical," "horizontal," "inner," and "outer," etc., indicate the orientation or positional relationship based on the orientation or positional relationship shown in the accompanying drawings, and are only for the convenience of describing the invention and simplifying the description, and do not indicate or imply that the device or element referred to must have a specific orientation, or be constructed and operated in a specific orientation, and therefore should not be construed as a limitation of the invention.

[0060] Unless otherwise explicitly specified and limited, the terms "installation," "connection," and "linking" should be interpreted broadly. For example, they can refer to fixed connections, detachable connections, or integral connections; they can refer to mechanical connections or electrical connections; they can refer to direct connections or indirect connections through an intermediate medium; and they can refer to the internal connection between two components. Those skilled in the art will understand the specific meaning of the above terms in this invention based on the specific circumstances.

[0061] This embodiment first discloses a transmission and reflection unit for an antenna, capable of transmitting and reflecting signals of a preset frequency. Please refer to... Figures 1 to 4 The transmission and reflection unit of the antenna includes a reflective patch 1, a first substrate 21, a first grating layer 31, a second substrate 22, a transmission patch 4, a third substrate 23, and a second grating layer 32.

[0062] The reflective patch 1 includes a first I-shaped patch 11 and two C-shaped patches 12 symmetrically arranged on both sides of the middle of the first I-shaped patch 11. The two C-shaped patches 12 are the same in shape and size. The bottom of the C-shaped patch 12 is parallel to the central branch of the first I-shaped patch 11, and the opening of the C-shaped patch 12 faces away from the first I-shaped patch 11. Adjusting the bottom length of the C-shaped patch 12 can adjust the phase shift value generated by the transmission and reflection unit when reflecting the X-polarized signal.

[0063] The first gate layer 31 consists of several metal strips running parallel to the length of the first I-shaped patch 11, and the second gate layer 32 consists of several metal strips perpendicular to the first gate layer 31. Figure 1 It can be seen that the metal strip of the first gate layer 31 is arranged along the X-axis direction, the metal strip of the second gate layer 32 is arranged along the Y-axis direction, and the transmission patch 4 is disposed between the first gate layer 31 and the second gate layer 32. The first gate layer 31 and the second gate layer 32 are mutually orthogonal metal strips, which on the one hand separate the incident waves polarized along the X-axis and those polarized along the Y-axis, giving the transmission and reflection unit polarization selectivity; on the other hand, their orthogonal placement forms a Fabry cavity effect, which can enhance the transmission amplitude of the unit.

[0064] The transmissive patch 4 includes a second I-shaped patch 41, a square patch 42, and two rectangular patches 43 connected in sequence. The two ends of the second I-shaped patch 41 are open-ended arc-shaped pieces. The length direction of the second I-shaped patch 41 forms a 45° angle with the length direction of the first gate layer 31. The square patch 42 is centrally located and perpendicular to the middle of the second I-shaped patch 41, with its centerline coinciding with the centerline of the second I-shaped patch 41. The two rectangular patches 43 are centrally located on either side of the square patch 42, i.e., on either side of the centerline of the second I-shaped patch 41. Adjusting the length of the rectangular patches 43 and the setting angle of the transmissive patch 4 can adjust the phase shift value generated by the transmissive-reflective unit when transmitting a Y-polarized signal. Figure 1As shown, the transmissive patch 4 is set at a 45° angle along its length, and the angle between its length direction and the Y-axis is... , At that time Figure 2 The state shown is as follows. At that time Figure 3 The state shown.

[0065] The antenna's transmission and reflection elements have good reflection and transmission performance, and can generate a phase shift value within a preset range by changing its own structural parameters.

[0066] As one implementation, the phase shift value generated by the transmission and reflection unit when reflecting the X-polarized signal The bottom length of C-shaped patch 12 The relationship is: .

[0067] , The length of the middle branch of the first I-shaped patch 11, The width of the two sides of the C-shaped patch 12, The distance between the side of the C-shaped patch 12 and the first I-shaped patch 11 is the distance between the side of the C-shaped patch 12 and the first I-shaped patch 11. In other words, the length of the first I-shaped patch 11 changes synchronously with the size of the C-shaped patch 12.

[0068] The phase shift value generated by the transmission and reflection unit when transmitting a Y-polarized signal and , and The relationship is:

[0069] hour, ;

[0070] hour, ;

[0071] , ;

[0072] In the formula, S As an intermediate parameter, The length of the rectangular patch is 43. To set the angle for the transmission patch 4, The angle is the angle between the center and end of the arc-shaped piece and the center of the second I-shaped patch 41.

[0073] In one embodiment, an air layer 5 is provided between the first substrate 21 and the second substrate 22. The provision of this air layer 5 enables the phase shift value to be adjusted. The bottom length of the C-shaped patch 12 When the change occurs, the trend is relatively gentle, which is beneficial for controlling phase compensation.

[0074] In a specific transmission and reflection unit, the width of the metal strips constituting the first grid layer 31 and the second grid layer 32 is 1.01 mm, and the spacing between the metal strips is 0.32 mm. The width of each branch in the first I-shaped patch 11 and the width of the two sides of the C-shaped patch 12 are both 0.2 mm, and the bottom width of the C-shaped patch 12 is 0.3 mm. The width of each branch in the second I-shaped patch 41 and the width of the rectangular patch 43 are both 0.3 mm. The width direction of the rectangular patch 43 is parallel to the length direction of the second I-shaped patch 41. The side length of the square patch 42 is 1.4 mm. The thickness of the air layer 5 is 0.6 mm. Other dimensional parameters are detailed in Table 1 below, where all values ​​are in mm.

[0075] Table 1:

[0076]

[0077] The transmission and reflection units of the above-described specific dimensions can be applied within a broadband range of 20-34 GHz. When the polarization of an electromagnetic wave is parallel to the aforementioned grating layer, the electromagnetic wave will be reflected back with the same polarization; when the polarization of the electromagnetic wave is perpendicular to the aforementioned grating layer, most of the energy will be transmitted, with only a small portion reflected back. Using the aforementioned grating layer, polarization can be effectively separated, allowing for the manipulation of electromagnetic waves with individual polarizations. Figure 5 The polarization separation effect of the two gate layers is shown.

[0078] In this embodiment, when the first gate layer 31 and the second gate layer 32 are placed orthogonally together, they form an effect similar to a Fabry cavity. When the dielectric thickness and gate layer design are appropriate, the transmission amplitude of electromagnetic waves can be increased, i.e., the transmission bandwidth is increased. With the above-mentioned dimensional parameters, the transmission amplitude can be significantly improved. Specifically... Figure 6 The influence of the presence or absence of these two grating layers on the transmission amplitude was analyzed. As shown in the figure, without these two grating layers, the transmission amplitude is very low in the 20-34 GHz band when the value of parameter S is changed, generally less than 0.5, indicating that most of the energy is reflected back. After introducing these two grating layers, changing the value of parameter S significantly improves the transmission amplitude in the 20-34 GHz band, with most frequencies exceeding 0.8, achieving a highly efficient transmission effect.

[0079] The air layer 5 provided in this embodiment enables the phase shift value to be... The bottom length of the C-shaped patch 12 When the change occurs, the trend is relatively gradual, which is beneficial for controlling phase compensation. Specifically, for example... Figure 7As shown, the influence of the presence or absence of air layer 5 on the reflection phase was analyzed. Without air layer 5, although the phase change can reach 360 degrees, the phase change trend is very steep, which increases the phase compensation error. With the introduction of air layer 5, the phase change range reaches 360 degrees, and the phase change is more gradual, which is more conducive to controlling phase compensation.

[0080] Furthermore, to better understand the broadband working mechanism of this transmission-reflection unit, the current distribution of the transmission patch 4 and the reflection patch 1 at 22GHz, 26GHz, and 32GHz frequencies with initial phase was tested. As shown in Figures 8 and 9, Figure 8 shows the current distribution of the transmission patch 4. It can be seen from the figure that there are similar current distributions at 22GHz, 26GHz, and 32GHz, meaning that changing the parameter S of the transmission structure results in similar current changes. This similarity leads to similar current amplitudes and responses at each frequency, thus achieving a broadband transmission effect. Similarly, Figure 9 shows the current distribution of the reflection structure. It can be seen from the figure that there are also similar current distributions at 22GHz, 26GHz, and 32GHz frequencies. Changing the parameters of the reflection structure also results in similar current changes, leading to similar current amplitudes and responses, thus achieving a broadband reflection effect.

[0081] Figure 10a The relationship between the transmission phase and the change of S is shown. Figure 10b The relationship between transmission amplitude and S is shown. Figure 10c The transmission phase and Relationship, Figure 10d The transmission amplitude and The changing relationship.

[0082] from Figure 10a As can be seen, by adjusting the value of parameter S, a phase coverage of more than 180 degrees can be obtained within the 22-32 GHz range. Then, due to the 45-degree oblique symmetry of the transmission patch 4, when... At 45 degrees and -45 degrees, the transmission patch 4 produces a phase difference of 180 degrees. Therefore, a transmission phase coverage range greater than 360 degrees can be obtained. Figure 10b and Figure 10d It can be seen that S changes from 3 to 10. With values ​​varying arbitrarily within ±45 degrees, the transmission amplitude is generally greater than 0.75, with only slightly lower frequencies at the two ends, but still greater than 0.6. In summary, by adjusting parameters S and... The value allows the transmissive patch 4 to achieve wide phase coverage and high efficiency across a broad frequency band of 22-32 GHz. In this embodiment, the transmissive-reflective unit achieves good transmission phase and amplitude response in the 22-32 GHz range; and good reflection phase and amplitude response in the same range. Furthermore, the phase control for transmission and reflection is independent, with phase ranges greater than 360 degrees, and nearly parallel phase responses across a wide operating frequency band, exhibiting broadband and high efficiency characteristics.

[0083] Figure 11a The reflection phase and The changing relationship, Figure 11b The reflection amplitude and The relationship between the changes is shown in the graph. As can be seen from the graph, the control... The value varies from 0.3mm to 2.7mm, and it can be found that there is a good phase response in the 22-32GHz range, with a phase change range greater than 360 degrees. At the same time, the reflection amplitude is greater than 99%, indicating that the reflective unit has broadband and high-efficiency reflection characteristics.

[0084] In this embodiment, a transmissive-reflective array antenna is also disclosed, such as... Figures 12 to 15 As shown, the transmissive-reflective array antenna includes M×N transmissive-reflective elements as described above and a feed source, with the feed source positioned on the side of the transmissive-reflective elements near the reflective patch 1. Figure 12 The feed offset setting for radiating X-axis polarized waves is intended to clearly demonstrate the principles of reflection and transmission. In actual products, only one feed is needed to radiate Y-axis and X-axis polarized waves. M and N are natural numbers not less than 1, and M×N is not less than 2. M and N represent the number of rows and columns in the array antenna. The larger the values ​​of M and N, the better the antenna performance.

[0085] This transmissive-reflective array antenna comprises an M×N array of several of the aforementioned transmissive-reflective elements. It features wide bandwidth, high gain, and multi-mode characteristics, which can improve the performance of communication systems and enable more efficient signal transmission in complex NLOS propagation environments.

[0086] In one specific embodiment, M×N is 25×25, the array size is 100mm×100mm×2.214mm, and the focal diameter ratio F / D=1, meaning the height of the feed source from the array is 100mm. The feed source is positioned directly below the array and is powered by a rectangular waveguide horn with a gain of 15dBi. Each substrate uses Rogers 5880 board material with a thickness of 0.508mm. Its function is that when the incident wave is a Y-axis polarized wave, the spherical wavefront electromagnetic wave emitted by the feed source can pass through the reflective patch 1 and the first grating layer 31, then reach the transmission array layer 7 for phase compensation before being transmitted as a plane wave, forming a high-gain pencil-shaped beam behind the array, achieving 0-degree focused transmission. When the incident wave is an X-axis polarized wave, when the spherical wavefront electromagnetic wave emitted by the feed placed at a 20-degree angle reaches the reflective array layer, the reflective unit performs phase compensation on the incoming wave and reflects it out in the form of a plane wave, forming a high-gain pencil-shaped beam in front of the array, achieving a 20-degree focused reflection.

[0087] Phase compensation values ​​required for each transmission and reflection unit for:

[0088]

[0089] In the formula, This represents the position of each transmission and reflection unit. The location of the feed source, i Indicating that each of the aforementioned transmission and reflection units is in x shaft and y The number of the axial direction. The direction of the pencil-shaped beam. The wavelength of the radiated electromagnetic wave is denoted as λ. Figure 16 The phase compensation for each of the transmission patches 4 is shown. Figure 17 The phase compensation of each reflective patch 1 is shown.

[0090] Figure 18 The simulation results for the HFSS simulation of this transmissive-reflective array antenna show that the antenna can support dual-polarized feed. When the feed polarization is Y-axis polarized, the electromagnetic wave can pass through the array and generate a pencil-shaped beam behind it. When the feed polarization is X-axis polarized, the electromagnetic wave will be reflected back and generate a pencil-shaped beam in a 20-degree direction. This indicates that the antenna's function is basically consistent with expectations and has good beam control capability.

[0091] like Figure 19As shown, the maximum gain of the transmitted beam is 25.6 dBi, corresponding to a peak aperture efficiency of 38%, and a 1-dB gain bandwidth of 22-30 GHz (31%). The maximum gain of the reflected beam is 25.1 dBi, with a peak aperture efficiency of 33% and a 1-dB gain bandwidth of 22-30 GHz (31%). This demonstrates that the transmittance-reflection array antenna possesses wide bandwidth, high gain, and high aperture efficiency. It also shows that each transmittance-reflection element can provide good phase compensation over a wide frequency range, exhibiting broadband and high-efficiency characteristics.

[0092] like Figures 20a to 20c The normalized 2D radiation patterns of the transmitted beam at 22 GHz, 26 GHz, and 30 GHz are shown. As can be seen from the figures, the first lobe level and cross-polarization level at 22 GHz are -18.7 dB and -20 dB, respectively; at 26 GHz, they are -23 dB and -22.8 dB, respectively; and at 30 GHz, they are -22.5 dB and -22.7 dB, respectively. Therefore, all three frequencies exhibit narrow beamwidths with good sidelobe suppression and high cross-polarization levels. This demonstrates that the transmission array 7 in this antenna maintains good performance over a wide frequency band.

[0093] like Figures 21a to 21c The normalized 2D radiation patterns of the reflected beam at 22 GHz, 26 GHz, and 30 GHz are shown. As can be seen from the figures, the beam direction is all in the direction of theta = 20 degrees. The first lobe level and cross-polarization level at 22 GHz are -15 dB and -26 dB, respectively; at 26 GHz, they are -16 dB and -23 dB, respectively; and at 30 GHz, they are -12 dB and -28.5 dB, respectively. The cross-polarization level is less than -23 dB in all three frequencies, indicating good performance. Therefore, all three frequencies exhibit narrow beams with high cross-polarization levels. This demonstrates that the reflective array 6 maintains good performance over a wide frequency band.

[0094] This antenna achieves a high-gain pencil-shaped transmitted beam at Theta = 0 degrees and a high-gain pencil-shaped reflected beam at Theta = 20 degrees. Within the operating frequency band, the maximum gains of the transmitted and reflected beams are 25.6 dBi and 25 dBi, respectively, while their 1-dB gain bandwidths are both 31%, and their aperture efficiencies are 38% and 33%, respectively. This indicates that the antenna possesses the characteristics of wide bandwidth, low gain ripple, and high aperture efficiency.

[0095] This antenna boasts a significant advantage: a wide 1-dB gain bandwidth. This means it can maintain stable high-gain output over a broad frequency range. This wide bandwidth allows the antenna to better adapt to frequency-selective fading in complex propagation environments, enabling efficient power transfer across multiple frequency bands. Even in complex NLOS propagation environments where some directions are blocked, the wide gain bandwidth ensures good performance in other available frequency bands, thereby improving the reliability and stability of signal transmission.

[0096] In another embodiment, the transflective array antenna is configured to output an OAM vortex beam, the various states of which ensure that electromagnetic waves in different OAM states are orthogonal to each other. This characteristic allows the OAM vortex beam to increase the capacity of wireless communication systems and improve their anti-interference capabilities, thus making OAM an important component of next-generation communications. This transflective array antenna can support outputting an OAM vortex beam and possesses good radiation performance.

[0097] Specifically, the transmission array 7 implementation mode l =+1 OAM vortex beam, reflected array 6 to achieve mode l =-1 OAM vortex beam. The required phase compensation value for each of the aforementioned transmission and reflection units. for:

[0098]

[0099] In the formula, The positions of each of the aforementioned transmission and reflection units. The location of the feed source, i Indicating that each of the aforementioned transmission and reflection units is in x shaft and y The number of the axial direction. The wavelength of the radiated electromagnetic wave is denoted as λ. The direction of the OAM vortex beam. l In OAM mode, under transmission state l =+1, in the reflection state l =-1. Figure 22 The phase compensation for each of the transmission patches 4 is shown. Figure 23 The phase compensation of each reflective patch 1 is shown. Correspondingly, the transmission array 7 composed of each transmission patch 4 is detailed below. Figure 24 For details of the reflective array 6 composed of individual reflective patches 1, please refer to [link / reference]. Figure 25 .

[0100] When an X-axis polarized incident wave strikes the array, the array transmits the electromagnetic wave, thus achieving mode. l=+1 OAM vortex beam effect, when a Y-axis polarized incident wave shines on the array, the array reflects the electromagnetic wave, thus realizing the mode. l =-1 OAM vortex beam effect. Furthermore, this effect is present across a wide operating frequency band, and the achieved OAM vortex beam exhibits high mode purity.

[0101] Figure 26 This shows the antenna in transmission mode. l In the +1 mode, the 3D radiation pattern, near-field amplitude, and phase distribution of the OAM vortex beam at 22GHz, 26GHz, and 30GHz are shown in the figure. As can be seen from the figure, the OAM vortex beam was achieved at all three frequency points. l The radiation effect of the +1 mode exhibits good consistency. Meanwhile, the mode purity of the antenna at the 26GHz frequency point is as... Figure 27 As shown in the figure, the following are considered l =-5 to l = +5 There are a total of 11 OAM modes. As can be seen from the figure, the 1 mode of the designed transmission OAM accounts for the majority, with a mode purity greater than 0.9. The other modes account for a very small proportion, indicating that the designed transmission OAM vortex beam has good 1 mode purity. The 1 mode transmission OAM vortex beam has the characteristics of wide bandwidth, good consistency and high mode purity.

[0102] Figure 28 The antenna in reflection state is shown. l In the -1 mode, the 3D radiation pattern, near-field amplitude, and phase distribution of the OAM vortex beam at 22 GHz, 26 GHz, and 30 GHz are shown in the figure. As can be seen from the figure, the OAM vortex beam was achieved at all three frequency points. l The radiation effect in the -1 mode exhibits good consistency. Meanwhile, the mode purity of the antenna at the 26GHz frequency point is as... Figure 29 As shown in the figure, the following are considered l =-5 to l = +5 There are a total of 11 OAM modes. As can be seen from the figure, the -1 mode of the designed reflection OAM accounts for the majority, with a mode purity greater than 0.85. The other modes account for a very small proportion, indicating that the designed reflection OAM vortex beam has good -1 mode purity. The -1 mode reflection OAM vortex beam has the characteristics of wide bandwidth, good consistency and high mode purity.

[0103] It will be apparent to those skilled in the art that the present invention is not limited to the details of the exemplary embodiments described above, and that the invention can be implemented in other specific forms without departing from its spirit or essential characteristics. Therefore, the embodiments should be considered illustrative and non-limiting, and the scope of the invention is defined by the appended claims rather than the foregoing description. Thus, all variations falling within the meaning and scope of equivalents of the claims are intended to be included within the present invention. No reference numerals in the claims should be construed as limiting the scope of the claims.

Claims

1. A transmissive reflective unit of an antenna, characterized by The reflective patch, the first substrate, the first grid layer, the second substrate, the transmissive patch, the third substrate and the second grid layer are sequentially arranged. The reflective patch comprises a first E-shaped patch and two C-shaped patches symmetrically arranged at both sides of the middle part of the first E-shaped patch, the bottom of the C-shaped patch is parallel to the center branch of the first E-shaped patch, and the opening direction of the C-shaped patch is away from the first E-shaped patch; and the length of the bottom of the C-shaped patch can be adjusted to adjust the phase shift value generated by the transmissive-reflection unit when reflecting an X-polarized signal. The first grid layer comprises a plurality of metal strips parallel to the length direction of the first E-shaped patch, and the second grid layer comprises a plurality of metal strips perpendicular to the first grid layer. The transmissive patch comprises a second E-shaped patch, a square patch and two rectangular patches which are sequentially connected, the two ends of the second E-shaped patch are arc-shaped patches with opposite openings, the length direction of the second E-shaped patch forms a 45° angle with the length direction of the first grid layer, the square patch is vertically arranged at the middle part of the second E-shaped patch, and the two rectangular patches are respectively arranged at the two sides of the square patch; and the length of the rectangular patch and the arrangement angle of the transmissive patch can be adjusted to adjust the phase shift value generated by the transmissive-reflection unit when transmitting a Y-polarized signal.

2. The transmissive-reflection unit of claim 1, wherein The phase shift value generated by the transreflective unit when reflecting an X-polarized signal The length of the base of the C-patch is related by: 。 3. The transmissive-reflection unit of claim 1, wherein The phase shift value generated by the transmissive reflective unit when transmitting a Y polarized signal With , And The relationship is: time, ; Time, ; ， ； In the formula, S is an intermediate parameter, is the length of the rectangular patch, is the setting angle of the transmission patch, is the included angle between the center and the end of the arc-shaped patch and the line connecting the centers of the second I-shaped patch.

4. The transmissive-reflection unit of claim 1, wherein An air layer is arranged between the first substrate and the second substrate.

5. A trans-reflective array antenna characterized by, Comprises: M×N transmissive-reflection units of any one of claims 1 to 4, M and N are natural numbers not less than 1, and M×N is not less than 2; A feed source is arranged on the side of the transmissive-reflection unit close to the reflective patch.

6. The transmissive-reflection array antenna of claim 5, wherein The thickness of the air layer in the transmissive-reflection unit is 0.6 mm.

7. The transmissive-reflection array antenna of claim 6, wherein M×N is 25×25, the size of the array is 100 mm×100 mm×2.214 mm, and the focal ratio F / D is 1.

8. The transmissive-reflection array antenna of claim 7, wherein The width of the metal strip is 1.01 mm, the pitch of the metal strip is 0.32 mm, the width of each branch in the first E-shaped patch and the width of the two sides of the C-shaped patch are both 0.2 mm, the width of the bottom of the C-shaped patch is 0.3 mm, the width of each branch in the second E-shaped patch and the width of the rectangular patch are both 0.3 mm, the width direction of the rectangular patch is parallel to the length direction of the second E-shaped patch, and the side length of the square patch is 1.4 mm.

9. The transmissive-reflection array antenna of claim 8, wherein The transreflective array antenna is arranged to output a pencil beam, and each of the transreflective units needs to generate a phase compensation value is: wherein is the position of each of the transreflective elements, is the position of the feed, is the direction of the pencil beam, is the wavelength of the radiated electromagnetic wave.

10. The transmissive-reflection array antenna of claim 8, wherein The transmissive-reflection array antenna is configured to output an OAM vortex beam, and each of the transmissive-reflection units needs to generate a phase compensation value is: wherein is the position of each of the transreflective elements, is the position of the feed, is the direction of the OAM vortex-like beam, l is the mode of OAM, in the transmissive state l = +1, in the reflective state l = -1, is the wavelength of the radiated electromagnetic wave.

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