Capacitance phase-shifting motor system circuit

Abstract

The invention discloses a capacitor phase-shifting motor system circuit, which is characterized in that after a current signal of a main winding is subjected to phase-shifting rectification, the amplitude of an auxiliary phase voltage is corrected by opening a resistor and a capacitor loop to adjust the current of an auxiliary phase voltage signal; comparing the amplitude potentials of the secondary phase voltage wave at different stages with the potential of a current signal for electrifying the secondary winding to synchronously control the current input quantity of the secondary winding; comparing the amplitude potentials of the secondary phase voltage wave at different stages with the potentials of the resistance and capacitance delay discharge loops, and synchronously obtaining the interruption delay time of the secondary phase current; the carrier direction of the secondary winding is restored by power supply voltage phase shift; and the secondary winding finally obtains a digital wave driving power supply of which the input size is controlled by the main phase input current. Therefore, as the main winding is directly driven by the power supply, the current of an electronic circuit is halved, the problem of interference of a bridge rectification filter gate circuit to the power supply is effectively solved, and the torque and efficiency of the motor are improved.

Description

Technical Field

[0001] This invention relates to the field of motor technology, and specifically to a capacitor phase-shifting motor system circuit. Background Technology

[0002] Existing capacitor motors use a capacitor phase-shifting circuit to directly drive the secondary winding. The power supply voltage amplitude causes a high amplitude in the secondary phase during the 0° to 45° phase period. However, when the power supply phase reaches 90° to 135°, the secondary phase voltage amplitude is zero, resulting in a high-potential standby time for the main winding. This leads to a significant decrease in both the motor's torque output and efficiency. Furthermore, the motor's input current amplitude leads the power supply voltage by 45°, causing serious power supply pollution. Similarly, Chinese patent "A Cable Structure for a Capacitor Motor Winding and Its Working Method" (patent number CN2020101769308), which also uses a phase-shifting circuit to drive the secondary winding, utilizes the current induction of the secondary winding to shunt the main winding, reorganizing the main phase excitation electrodes to change the main phase excitation phase. Under normal circumstances, this increases the torque output of the main phase at 45° and 135°. However, during the 90° to 135° phase of the main phase potential, the secondary phase voltage amplitude remains zero, and during this period, there is no input current from the secondary phase to shunt the main winding.

[0003] Currently, only the bridge drive winding method used in variable frequency motors can solve the problem of secondary winding drive defects in capacitor motors; however, this drive method has problems such as large heat generation of bridge components, current input concentrated in the peak stage of power supply voltage, and interference with the power supply; if a single-phase frequency converter is selected to drive a three-phase motor, there are problems such as high cost, inability to integrate the frequency converter and motor into one unit resulting in loss of convenience, particularly large power supply interference, and limited starting current. Summary of the Invention

[0004] In view of the above-mentioned shortcomings of the existing technology, the present invention provides a capacitor phase-shifting motor system circuit. Through the innovation of drive architecture, optimization of heat dissipation integration, improvement of control accuracy and improvement of protection mechanism, the capacitor phase-shifting motor system circuit has the characteristics of high efficiency, reliability and low cost, and effectively overcomes the problems existing in the prior art.

[0005] To solve the above-mentioned technical problems, the present invention adopts the following technical solution: This invention provides a capacitor phase-shifting motor system circuit, including a main winding, a secondary winding, and a digital wave drive power supply with a 90° phase shift. The main winding is directly driven by an AC power supply, and the secondary winding is driven by the digital wave drive power supply with a 90° phase shift. The key feature is that the AC power supply is rectified by a power rectifier bridge Q and stepped down by a resistor R4 to form a carrier voltage. The carrier voltage is then applied to both ends of the secondary winding through a carrier direction drive circuit to control the direction and amplitude of the carrier voltage applied to the secondary winding. The secondary winding carrier direction drive circuit includes a secondary winding carrier drive circuit, a secondary winding carrier direction signal circuit, a secondary winding carrier amplitude circuit, and a switching power supply circuit. The secondary winding carrier drive circuit includes a bridge circuit composed of four IC modules. The four IC modules are IC2 (upper bridge transistor) and IC3 (lower bridge transistor) on the forward carrier side, and IC1 (upper bridge transistor) and IC4 (lower bridge transistor) on the reverse carrier side. Each IC module is a module circuit that uses an optocoupler to isolate and control the on / off state of a field-effect transistor. The two ends of the secondary winding are designated as terminals A and B. The two output terminals of the field-effect transistor in IC2 (upper bridge transistor) on the forward carrier side are connected to the DC cathode of the power rectifier bridge Q and terminal A of the secondary winding, respectively. The two output terminals of the field-effect transistor in IC3 (lower bridge transistor) on the forward carrier side are connected to terminal B of the secondary winding and connected to the DC anode of the power rectifier bridge Q via resistor R4. The two output terminals of the field-effect transistor in IC1 (upper bridge transistor) on the reverse carrier side are connected to the DC cathode of the power rectifier bridge Q, respectively. The two output terminals of the field effect transistor in IC1 of the bridge on the reverse carrier side are connected to the A terminal of the secondary winding and the DC anode terminal of the power rectifier bridge Q through resistor R4, respectively. The input sides of the optocouplers in the two IC modules on the positive carrier side are connected in series to one of the carrier direction signal output terminals of the secondary winding carrier direction signal circuit. The input sides of the optocouplers in the two IC modules on the reverse carrier side are connected in series to the other of the carrier direction signal output terminals of the secondary winding carrier direction signal circuit. Thus, the two IC modules on the positive carrier side or the two IC modules on the reverse carrier side in the secondary winding carrier drive circuit are turned on by the different carrier direction signals of the secondary winding carrier direction signal circuit, so that the current direction formed by the carrier voltage flows from the A terminal to the B terminal of the secondary winding, or from the B terminal to the A terminal of the secondary winding. The secondary winding carrier direction signal circuit extracts voltage from the AC power supply terminals and converts it into DC power supply output to the switching power supply circuit through rectification and conversion. By phase shifting the DC power supply, two different carrier direction signals are generated and output to the secondary winding carrier drive circuit. The secondary winding carrier amplitude circuit extracts the voltage across the current sensing coil H of the main winding, and after phase shifting, rectification, and delay processing, forms a carrier amplitude signal, which is used to provide bias voltage to the field-effect transistors of the two lower bridge transistors in the secondary winding carrier drive circuit, thereby dynamically controlling the amplitude of the secondary winding input voltage and the amplitude of the input current. The switching power supply circuit is used to perform isolation voltage conversion on the DC power supply to form a first isolated DC power supply V1, a second isolated DC power supply V2, and a third isolated DC power supply V3 with a first set voltage value, and to step down the first isolated DC voltage to a low-voltage DC voltage V0 with a second set voltage value; wherein, the first isolated DC power supply V1 is output to the delay processing circuit in the secondary winding carrier amplitude circuit; the second isolated DC power supply V2 and the third isolated DC power supply V3 are respectively used to provide bias voltage to the field-effect transistors on the two bridge transistors in the secondary winding carrier drive circuit; the low-voltage DC voltage V0 is output to the DC anode terminal of the power rectifier bridge Q and the DC anode terminal of the rectifier in the secondary winding carrier amplitude circuit to cancel the potential difference.

[0006] As a preferred embodiment, each IC module is controlled by an optocoupler to isolate the on / off state of the field-effect transistor, and has 6 connection pins, wherein pins 1 and 2 are the input-side anode and input-side cathode of the optocoupler in the IC module, pins 3 and 4 are the bias voltage and negative bias power supply of the field-effect transistor in the IC module, and pins 5 and 6 are the two output connection terminals of the field-effect transistor in the IC module.

[0007] As a preferred embodiment, the specific circuit structure of each IC module includes an optocoupler OC, a field-effect transistor M, a diode d, a Zener diode W, a bias resistor r1, a trigger resistor r2, and transistors b1, b2, b3, b4, and b5. The drain of the field-effect transistor M is led out from pin 5 of the IC, the source of the field-effect transistor M is led out from pin 6 of the IC, and the gate of the field-effect transistor M is connected to the emitters of transistors b3 and b4. The bases of transistors b3 and b4 are connected to the collector of transistor b5, the anode of diode d, and the emitter of transistor b2. The collector of transistor b4 is connected to the base of transistor b5, the emitter of transistor b5 is connected to pin 4 of the IC module, and the collector of transistor b3 is connected to the field-effect transistor OC. The bias power supply for transistor M is connected to the base of transistor b2, which is connected to the collector of transistor b1. The emitter of transistor b1 is connected to the emitter of optocoupler OC, the cathode of diode d, and one end of bias resistor r1. The other end of bias resistor r1 is grounded. The collector of transistor b2 is connected to the base of transistor b1 and the cathode of Zener diode W. The anode of W is connected in series with trigger resistor r2 and then to pin 4 of IC module. The collector of optocoupler OC is connected to pin 3 of IC module. The positive terminal of the bias power supply for MOSFET M is input from pin 3 of IC module, and the negative terminal of the bias power supply for MOSFET M is connected to pin 4 of IC module. The anode of diode in optocoupler OC is connected to pin 1 of IC module, and the cathode of diode in optocoupler OC is connected to pin 2 of IC module.

[0008] As a preferred embodiment, in the specific circuit structure of the secondary winding carrier drive circuit, pins 5 of the upper transistors IC1 and IC2 of the bridge are connected to the positive terminal of the filter capacitor C and the DC negative terminal of the power rectifier bridge Q; pins 4 and 6 of the upper transistor IC1 are connected, and then pin 5 of the lower transistor IC3 is connected to the B terminal of the secondary winding and the negative terminal of the second isolation DC power supply V2; the positive terminal of the second isolation DC power supply V2 is connected to pin 3 of the upper transistor IC1; pins 4 and 6 of the upper transistor IC2 are connected, and then pin 5 of the lower transistor IC4 is connected to the A terminal of the secondary winding and the negative terminal of the third isolation DC power supply V3; the positive terminal of the third isolation DC power supply V3 is connected to pin 3 of the upper transistor IC2; pins 6 of the lower transistors IC3 and IC4 are connected to the upper transistor IC2. After connection, series resistor R4 is connected to the negative terminal of filter capacitor C and the DC positive terminal of power rectifier bridge Q; pins 4 of lower bridge transistor IC3 and pins 4 of lower bridge transistor IC4 are connected to ground; pins 3 of lower bridge transistor IC3 and pins 3 of lower bridge transistor IC4 are connected to the carrier amplitude signal output terminal of the secondary winding carrier amplitude circuit; pins 1 of upper bridge transistor IC1 and pins 1 of upper bridge transistor IC2 are respectively connected to the output terminals of two different carrier direction signals of the secondary winding carrier direction signal circuit; pin 2 of upper bridge transistor IC1 is connected to pin 1 of lower bridge transistor IC4, and pin 2 of upper bridge transistor IC2 is connected to pin 1 of lower bridge transistor IC3; pins 2 of lower bridge transistor IC4 and pins 2 of lower bridge transistor IC3 are respectively connected to the return terminals of two different carrier direction signals of the secondary winding carrier direction signal circuit.

[0009] As a preferred embodiment, the secondary winding carrier direction signal circuit includes a rectifier bridge Q1, a phase-shifting capacitor C1, a filter capacitor C2, a delay capacitor C3, a delay capacitor C4, current-limiting resistors R1, R2, and R3, Zener diodes W1 and W2, delay switch transistors BG1 and BG2, and rectifier diodes D1 and D2; the AC terminal of the rectifier bridge Q1 is connected in series with the phase-shifting capacitor C1 and then connected to the two ends of the AC power supply; After the current-limiting resistor R1 is connected in series with the cathode of the rectifier bridge Q1, it serves as the common output terminal for the two different carrier direction signals of the secondary winding carrier direction signal circuit. The DC cathode and DC anode of the rectifier bridge Q1 are connected in parallel with the positive and negative terminals of the filter capacitor C2, respectively, serving as the positive terminal of the DC power supply and the isolation ground wire. The cathode of rectifier diode D1 is connected to one AC terminal of rectifier bridge Q1, and the cathode of rectifier diode D2 is connected to the other AC terminal of rectifier bridge Q1. The cathode of D1 is connected to one end of the current-limiting resistor R2. The other end of the current-limiting resistor R2 is connected to the cathode of the Zener diode W1, the anode of the rectifier diode D1, and one end of the delay capacitor C3. The other end of the delay capacitor C3 is connected to the isolation ground of the DC power supply. The cathode of the rectifier diode D2 is connected to one end of the current-limiting resistor R3. The other end of the current-limiting resistor R3 is connected to the cathode of the Zener diode W2, the anode of the rectifier diode D2, and one end of the delay capacitor C4. The other end of the delay capacitor C4 is connected to the isolation ground of the DC power supply. The anode of the Zener diode W1 is connected to the base of the delay switch BG1, and the anode of the Zener diode W2 is connected to the base of the delay switch BG2. The emitters of the delay switches BG1 and BG2 are connected and then connected to the isolation ground of the DC power supply. The collectors of the delay switches BG1 and BG2 serve as the return terminals for two different carrier direction signals of the secondary winding carrier direction signal circuit.

[0010] As a preferred embodiment, the secondary winding carrier amplitude circuit includes a rectifier bridge Q2, a phase-shifting capacitor C5, a trigger capacitor C6, a timing charging capacitor C7, a time-delayed discharge capacitor C8, a bias current resistor R5, a bias current resistor R6, a reset bias current resistor R7, an amplitude adjustment resistor R8, an amplitude adjustment resistor R9, and a time-delayed discharge resistor R1. 10 Current limiting resistor R 11 1. Switching transistor BG3, Reverse switching transistor BG4, Switching transistor BG5, Reset transistor BG6, Amplitude adjustment transistor BG7, Bias switching transistor BG8, Current comparison switching transistor BG9, Thyristor shutdown transistor BG 10The rectifier bridge Q2 consists of a reset diode D3, a trigger diode D4, an overload protection diode D5, and a thyristor K. The AC terminal of the rectifier bridge Q2 is connected in series with a phase-shifting capacitor C5 and then connected to the two ends of the current induction coil H of the main winding. The DC anode of the rectifier bridge Q2 is connected to a low-voltage DC voltage V0. Amplitude adjustment resistors R8 and R9 are connected in series, with one end connected to the DC cathode of the rectifier bridge Q2 and the other end grounded. The collector of the amplitude adjustment transistor BG7 is connected to the DC cathode of the rectifier bridge Q2. The emitter of transistor 7 is connected to the DC anode of rectifier bridge Q2. The base of amplitude regulating transistor BG7, connected in series with bias resistor R6 and timing charging resistor R6, is then connected to the first isolated DC power supply V1. The connection node between bias resistor R5 and bias resistor R6 is connected to the emitter of reverse switching transistor BG4 and the collector of switching transistor BG5. The emitter of switching transistor BG5 is connected to the emitter of reset transistor BG6 and one end of timing charging capacitor C7. The other end of timing charging capacitor C7 is connected to the rectifier bridge. The DC anode of Q2 is connected to the rectifier bridge; the collector of reset transistor BG6 is connected to the DC anode of rectifier bridge Q2, and the base of reset transistor BG6 is connected to the collector of reverse-biased switching transistor BG4, the base of switching transistor BG5, and one end of reset bias resistor R7. The other end of reset bias resistor R7 is connected to the DC anode of rectifier bridge Q2; the base of reverse-biased switching transistor BG4 is connected to the collector of switching transistor BG3, the emitter of switching transistor BG3 is grounded, and the base of switching transistor BG3 is connected to reset transistor BG4. The cathode of transistor D3 is connected to one end of trigger capacitor C6, and the other end of trigger capacitor C6 is connected to the DC cathode of rectifier bridge Q2. The anode of reset diode D3 is grounded. The emitter of bias switching transistor BG8 is connected to the first isolated DC power supply V1. The collector of bias switching transistor BG8 serves as the carrier amplitude signal output terminal of the secondary winding carrier amplitude circuit. The base of bias switching transistor BG8 is connected to the anode of thyristor K. The cathode of thyristor K is connected in parallel to the time-delay discharge capacitor C8 and the time-delay discharge resistor R. 10 After grounding, the cathode of the thyristor K is also connected to the thyristor shutdown transistor BG. 10 The collector of the thyristor K is connected to the cathode of the trigger diode D4, and the anode of the trigger diode D4 is connected to the DC cathode of the rectifier bridge Q2; the thyristor turns off transistor BG. 10 The emitter is connected to the first isolated DC power supply V1, and the thyristor shuts down the transistor BG. 10 The base is connected to the current-limiting resistor R. 11The collector of the current comparison switching transistor BG9 is connected to the collector of the current comparison switching transistor BG9. The emitter of the current comparison switching transistor BG9 is connected to the series junction of the amplitude adjustment resistor R8 and the amplitude adjustment resistor R9. The base of BG9 is connected to pin 6 of the lower transistor IC3 and the lower transistor IC4 in the secondary winding carrier drive circuit. The series junction of the amplitude adjustment resistor R8 and the amplitude adjustment resistor R9 is also connected to the anode of the overload protection diode D5. The cathode of the overload protection diode D5 is grounded.

[0011] As a preferred embodiment, the switching power supply circuit includes transformer E05, capacitor C9, and capacitor C. 10 Capacitor C 11 Capacitor C 12 Capacitor C 13 Resistance R 12 Resistance R 13 Resistance R 14 Zener diode W3, transistor BG 11 Transistor BG 12 Transistor BG 13 Diodes D6, D7, D8, and D9; the transformer E05 includes two primary coils and three secondary coils, namely a first primary coil, a second primary coil, a first secondary coil, a second secondary coil, and a third secondary coil; one end of the first primary coil is connected to the positive terminal of the DC power supply, and the other end of the first primary coil is connected to transistor BG. 11 The collector of the transistor BG 11 The emitter of the transistor is connected to the isolated ground of the DC power supply, and the transistor BG... 11 Base connection resistor R 12 One end of the resistor is connected to the cathode of the Zener diode W3, and the resistor R is connected to the cathode of the Zener diode W3. 12 The other end is connected to the positive terminal of the DC power supply, and the anode of the Zener diode W3 is connected to the capacitor C. 10 The negative terminal of diode D6 is connected to the anode of diode D6, and the cathode of diode D6 is connected to one end of the second primary coil. The other end of the second primary coil is connected to capacitor C. 10 The positive terminals of all components are connected to the isolated ground wire of the DC power supply; resistor R 13 After being connected in series with capacitor C9, one end is connected to transistor BG. 11 The base of the diode is connected to the cathode of diode D6 at the other end; the secondary coil is connected in series with diode D8 and then with capacitor C. 12 The two ends of the parallel connection serve as the positive and negative terminals of the second isolated DC power supply V2; the third stage coil is connected in series with diode D9 and then with capacitor C. 13 The two ends of the parallel connection serve as the positive and negative terminals of the third isolation DC power supply V3; the first primary coil is connected in series with diode D7 and then with capacitor C.11 Connected in parallel, the two ends of the parallel connection serve as the positive terminal and ground terminal of the first isolation DC power supply V1; transistor BG 13 The emitter of transistor BG is connected to the ground terminal of the first isolation DC power supply V1. 13 The collector of the transistor BG is connected. 12 The base and resistor R 14 One end, resistor R 14 The other end and transistor BG 12 The collectors of transistors BG are all connected to the positive terminal of the first isolated DC power supply V1. 12 emitter and transistor BG 13 After being connected to the base, it serves as the output terminal of the low-voltage DC voltage V0.

[0012] Compared with the prior art, the present invention has the following advantages: 1. The capacitor phase-shifting motor system circuit of this invention achieves electrode rearrangement of the main winding at 60°, 90°, and 120° phase periods through a collaborative design of digital wave drive for the auxiliary winding and direct AC power drive for the main winding, combined with the patented "capacitor motor winding wiring structure" technology. This design enables a two-phase motor to achieve the output torque level of a three-phase motor. Simultaneously, through the complementary effect of the main phase current and auxiliary phase current, a sinusoidal current consumption is formed, significantly reducing the interference of the rectifier filter circuit on the power supply. After the increased torque output of the motor at 60° and 120° phase periods, the terminal current and the auxiliary phase peak current consumption complement each other, improving overall efficiency and reducing heat dissipation and component costs to less than 1 / 3 of comparable frequency converters.

[0013] 2. In the capacitor-phase-shifted motor system circuit of this invention, during motor startup, the auxiliary winding is only limited by the maximum excitation current at certain phases, while the main winding achieves current-free drive within a 30° phase range through electrode arrangement adjustment, ensuring easy startup and minimizing component damage. The amplitude of the auxiliary phase voltage is dynamically adjusted via capacitor phase shifting using the main phase current signal: when the main phase potential rises, the auxiliary phase voltage moves in the same direction as the main phase, resulting in a higher torque output and a higher phase-shifted voltage amplitude; conversely, when the main phase potential falls, the auxiliary phase voltage reverses, resulting in a lower torque output and a higher phase-shifted voltage amplitude. This design effectively solves the problem of insufficient amplitude in the auxiliary phase from 0° to 45°, and simultaneously ensures the standard compliance of the auxiliary winding's auxiliary excitation of the main winding through dynamic adjustment of the load impedance.

[0014] 3. The capacitor phase-shifting motor system circuit of this invention uses a switching power supply bridge rectifier and filter circuit as the phase-shifting voltage load circuit. Utilizing its voltage gate circuit characteristics, when the AC input voltage is below the DC input voltage, the load impedance is extremely high, allowing for an instantaneous boost of the load voltage to the filter capacitor voltage, and shunting current to the optocoupler and switching power supply. Most major electronic components can be integrated into the motor terminal block, relying on the chassis for heat dissipation. Except for the DC filter capacitor, all other electronic components can be integrated, significantly reducing circuit costs (by more than 50%). Simultaneously, by adding a capacitor delay device to the optocoupler diode circuit, damage to the MOSFET caused by simultaneous activation of forward and reverse switches is avoided, improving system reliability.

[0015] 4. In the capacitor-phase-shifting motor system circuit of this invention, the carrier signal of the secondary winding is phase-shifted by a capacitor and rectified by a bridge circuit. Then, it is driven by a digital wave through a thyristor and a current comparison switching transistor to drive the field-effect transistor. Specifically, the carrier analog wave triggers the thyristor, and combined with a delayed discharge capacitor and a current comparison mechanism, achieves precise digital sinusoidal control of the secondary winding current: when operating at potential 1, the higher the carrier amplitude, the larger the secondary winding current; when operating at potential 0, the higher the carrier amplitude, the shorter the potential 0 time. This design synchronously increases the carrier amplitude by adjusting the potential across the timing capacitor and fixes the alternating amplitude of the resistive load during the potential drop phase, ensuring that the current control accuracy conforms to the frequency converter motor interruption concept. It also solves the problem of insufficient amplitude during the secondary phase voltage rise phase, improving the overall system efficiency and stability. Attached Figure Description

[0016] Figure 1 This is a diagram showing the carrier direction of the secondary winding and the driving circuit in the capacitor phase-shifting motor system circuit of the present invention; Figure 2 This is a diagram of the IC module in the capacitor phase-shifting motor system circuit of the present invention; Figure 3 This is a circuit diagram of the carrier amplitude of the secondary winding in the capacitor phase-shifting motor system of the present invention; Figure 4 This is a circuit diagram of the switching power supply in the capacitor phase-shifting motor system of the present invention. Detailed Implementation

[0017] To make the objectives, technical solutions, and advantages of the embodiments of the present invention clearer, the technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some, not all, of the embodiments of the present invention. The components of the embodiments of the present invention described and shown in the accompanying drawings can generally be arranged and designed in various different configurations. Therefore, the following detailed description of the embodiments of the present invention provided in the accompanying drawings is not intended to limit the scope of the claimed invention, but merely represents selected embodiments of the invention. All other embodiments obtained by those skilled in the art based on the embodiments of the present invention without inventive effort are within the scope of protection of the present invention.

[0018] It should be noted that similar reference numerals and letters in the following figures indicate similar items. Therefore, once an item is defined in one figure, it does not need to be further defined and explained in subsequent figures. In the description of this invention, it should be noted that the terms "center," "upper," "lower," "left," "right," "vertical," "horizontal," "inner," and "outer," etc., indicate the orientation or positional relationship based on the orientation or positional relationship shown in the figures, or the orientation or positional relationship commonly used when the product is in use. They are only for the convenience of describing the invention and simplifying the description, and do not indicate or imply that the device or element referred to must have a specific orientation, or be constructed and operated in a specific orientation. Therefore, they should not be construed as limitations on the invention. Furthermore, the terms "first," "second," and "third," etc., are only used to distinguish descriptions and should not be construed as indicating or implying relative importance. In addition, the terms "horizontal," "vertical," etc., do not indicate that the component is required to be absolutely horizontal or suspended, but can be slightly tilted. For example, "horizontal" simply means that its direction is more horizontal than "vertical," and does not mean that the structure must be completely horizontal, but can be slightly tilted. In the description of this invention, it should also be noted that, unless otherwise explicitly specified and limited, the terms "set," "install," "connect," and "link" should be interpreted broadly. For example, they can refer to a fixed connection, a detachable connection, or an integral connection; they can refer to a mechanical connection or an electrical connection; they can refer to a direct connection or an indirect connection through an intermediate medium; and they can refer to the internal connection of two components. Those skilled in the art can understand the specific meaning of the above terms in this invention based on the specific circumstances.

[0019] This invention provides a capacitor phase-shifting motor system circuit, including a main winding, a secondary winding, and a digital wave drive power supply with a 90° phase shift. The main winding is directly driven by an AC power supply, and the secondary winding is driven by the digital wave drive power supply with the 90° phase shift. The AC power supply, after rectification by a power rectifier bridge Q and voltage reduction by a resistor R4, forms a carrier voltage. This carrier voltage is then applied to both ends of the secondary winding through a carrier direction drive circuit to control the direction and amplitude of the carrier voltage applied to the secondary winding.

[0020] Specifically, the secondary winding carrier direction drive circuit includes a secondary winding carrier drive circuit, a secondary winding carrier direction signal circuit, a secondary winding carrier amplitude circuit, and a switching power supply circuit.

[0021] The secondary winding carrier drive circuit includes a bridge circuit composed of four IC modules. These four IC modules are IC2 (upper bridge transistor) and IC3 (lower bridge transistor) on the forward carrier side, and IC1 (upper bridge transistor) and IC4 (lower bridge transistor) on the reverse carrier side. Each IC module is a module circuit that uses an optocoupler to isolate and control the on / off state of the field-effect transistor. The two ends of the secondary winding are designated as terminals A and B. The two output terminals of the field-effect transistor in IC2 (upper bridge transistor) on the forward carrier side are connected to the DC cathode of the power rectifier bridge Q and terminal A of the secondary winding, respectively. The two output terminals of the field-effect transistor in IC3 (lower bridge transistor) on the forward carrier side are connected to terminal B of the secondary winding and connected to the DC anode of the power rectifier bridge Q via resistor R4. The two output terminals of the field-effect transistor in IC1 (upper bridge transistor) on the reverse carrier side are connected to the DC cathode of the power rectifier bridge Q. The two output terminals of the field effect transistor in IC1 of the bridge on the reverse carrier side are connected to the A terminal of the secondary winding and the DC anode terminal of the power rectifier bridge Q through resistor R4, respectively. The input sides of the optocouplers in the two IC modules on the forward carrier side are connected in series to one of the carrier direction signal output terminals of the carrier direction signal circuit of the secondary winding. The input sides of the optocouplers in the two IC modules on the reverse carrier side are connected in series to the other of the carrier direction signal output terminals of the carrier direction signal circuit of the secondary winding. Thus, the two IC modules on the forward carrier side or the two IC modules on the reverse carrier side in the carrier drive circuit are turned on by the different carrier direction signals of the carrier direction signal circuit of the secondary winding, so that the current direction formed by the carrier voltage flows from the A terminal to the B terminal of the secondary winding, or from the B terminal to the A terminal of the secondary winding.

[0022] The secondary winding carrier direction signal circuit extracts voltage from the AC power supply terminals and converts it into DC power supply output to the switching power supply circuit through rectification. By phase shifting the DC power supply, two different carrier direction signals are generated and output to the secondary winding carrier drive circuit.

[0023] The secondary winding carrier amplitude circuit extracts the voltage across the current sensing coil H of the main winding, and after phase shifting, rectification, and delay processing, forms a carrier amplitude signal, which is used to provide bias voltage to the field-effect transistors of the two lower bridge transistors in the secondary winding carrier drive circuit, thereby dynamically controlling the amplitude of the secondary winding input voltage and the amplitude of the input current.

[0024] The switching power supply circuit is used to perform isolation voltage conversion on the DC power supply to form a first isolated DC power supply V1, a second isolated DC power supply V2, and a third isolated DC power supply V3 with a first set voltage value, and to step down the first isolated DC voltage to a low-voltage DC voltage V0 with a second set voltage value. Among them, the first isolated DC power supply V1 is output to the delay processing circuit in the secondary winding carrier amplitude circuit; the second isolated DC power supply V2 and the third isolated DC power supply V3 are respectively used to provide bias voltage to the field-effect transistors on the two bridge transistors in the secondary winding carrier drive circuit; the low-voltage DC voltage V0 is output to the DC anode terminal of the power rectifier bridge Q and the DC anode terminal of the rectifier in the secondary winding carrier amplitude circuit to cancel the potential difference.

[0025] The capacitor phase-shifting motor system circuit provided by this invention achieves full-link optimization from drive architecture to protection mechanism through systematic innovative design, demonstrating significant technical advantages in terms of efficiency improvement, cost control, reliability enhancement and safety protection.

[0026] At the drive architecture level, this invention adopts a dual-winding cooperative drive mode, where the main winding is directly driven by AC power, and the secondary winding is driven by a digital wave driven by a 90° phase shift. A carrier voltage generation module, constructed by combining the power supply rectifier bridge Q and the step-down resistor R4, can rectify and step down the AC power supply to form a stable carrier voltage, which is then bidirectionally controllable via the secondary winding carrier direction drive circuit. This drive circuit employs a modular MOSFET bridge structure with optocoupler isolation control, comprising four IC modules: IC2 (upper transistor) and IC3 (lower transistor) on the forward carrier side, and IC1 (upper transistor) and IC4 (lower transistor) on the reverse carrier side. Each module is electrically isolated from the input and output signals by an optocoupler, effectively improving the circuit's anti-interference capability and reliability. The voltage signal at both ends of the AC power supply is extracted by the secondary winding carrier direction signal circuit. After rectification and conversion to DC power, it undergoes phase shifting to generate two independent carrier direction signals. These signals control the conduction state of the IC modules on the forward and reverse carrier sides, respectively, enabling precise switching of the carrier current direction from end A to end B or vice versa. Simultaneously, the secondary winding carrier amplitude circuit extracts the voltage signal from both ends of the main winding current sensing coil H. After phase shifting, rectification, and delay processing, it generates a carrier amplitude signal, which controls the bias voltage of the lower MOSFET in the bridge circuit of the secondary winding carrier drive circuit, achieving precise control of the carrier current amplitude. The switching power supply circuit performs multi-channel isolation voltage conversion on the DC power supply to generate a first isolated DC power supply V1 (used for the delay processing circuit in the secondary winding carrier amplitude circuit), a second isolated DC power supply V2, and a third isolated DC power supply V3 (used for the bias voltage of the two MOSFETs on the bridge in the secondary winding carrier drive circuit, respectively). The first isolated DC voltage is then stepped down to a low-voltage DC voltage V0 to offset the potential difference between the DC anode of the power supply rectifier bridge Q and the DC anode of the secondary winding carrier amplitude circuit rectifier, effectively solving the interference problem of the bridge rectifier filter gate circuit on the power supply.

[0027] Regarding heat dissipation integration and cost control, in the capacitor phase-shifting motor system circuit of this invention, except for the DC filter capacitor C, all other resistive components can be integrated into the motor terminal block. Relying on the motor housing for heat dissipation, the ease of use of the capacitor motor can be maintained, and the cost of the electronic circuit can be reduced by more than 50%. This integrated design not only reduces the need for external heat dissipation devices but also reduces the size and weight of the circuit, improving the system's compactness and reliability.

[0028] Regarding efficiency improvement, this invention utilizes the unidirectional wave voltage after phase shifting of the main phase induced current to control the secondary winding current, effectively solving the problem of insufficient amplitude of traditional phase-shifted voltage in the early stage of potential rise, thereby increasing motor torque and improving operating efficiency. This design reduces energy loss and improves the overall performance of the motor by optimizing the current waveform.

[0029] In terms of starting performance, the auxiliary winding adopts a current-limiting design with twice the rated current, while the main winding has no current limitation and its electrode arrangement curvature is twice that of the auxiliary winding. This ensures sufficient torque and controllable current during motor startup, achieving shock-free starting and reducing the risk of component damage. This design ensures the smoothness and safety of the motor during startup.

[0030] In terms of protection mechanisms, only an overheat protection switch needs to be installed on the main winding. When the main phase current is disconnected, the secondary phase current approaches zero, forming a dual safety protection mechanism. This design effectively prevents damage to the motor under overload or overheating conditions, further improving the safety and reliability of the system.

[0031] Furthermore, the capacitor phase-shifting motor system circuit of the present invention can also be combined with the stator winding method in the inventor's previously disclosed "A winding structure of a capacitor motor and its working method" (patent number CN2020101769308). This winding structure is as follows: first, the auxiliary winding is distributed in the stator core according to the concentric winding arrangement, with the electrode distribution range not exceeding a 45° phase angle; the main winding distribution consists of two parts, one of which is distributed at a 90° phase angle position of the auxiliary phase electrode, adjacent to the auxiliary winding. Two core slots are reserved; another part of the main winding is subdivided into shunt winding 1 and shunt winding 2. One electrode of shunt winding 1 is located in the core slot outside the secondary phase at 45°, and the other electrode is distributed and overlapped on the secondary winding electrode on the side of the secondary phase electrode closer to -45°; one electrode of shunt winding 2 is located in the core slot outside the secondary phase at -45°, and the other electrode is distributed and overlapped on the secondary winding electrode on the side of the secondary phase electrode closer to 45°; then the two shunt windings are connected in parallel according to the winding direction of the main winding and then connected in series with the first part of the main winding. By adopting the above stator winding structure, the load input of the main phase near the 60° and 120° phases can be increased. The increased current can complement the current input of the secondary phase during the peak of the power supply voltage, resulting in sinusoidal amplitude consumption, thereby eliminating the interference of the secondary phase current input to the power supply. At the same time, the main winding bears 2 / 3 of the load operation, while the secondary phase only bears 1 / 3 of the motor output load operation. This allows for the placement of the bridge drive components on the motor housing for heat dissipation, maintaining the motor's portability. The secondary winding uses the main phase current signal to shift the phase through a capacitor. This allows for the initial correction of the phase-shifted voltage wave amplitude by changing the torque output of the main phase. Further correction is achieved by changing the load current of the phase-shifted voltage wave. Finally, the phase potential of the corrected phase-shifted voltage wave during its change is used to synchronously limit the interruption of the secondary winding's input current and control the interruption time of the current. This system uses the main phase current to intelligently regulate the amplitude of the secondary phase input voltage and current.

[0032] Specifically, the specific circuit structure of the capacitor phase-shifting motor system circuit of the present invention is as follows: Figures 1 to 4 As shown.

[0033] The specific circuit structure of the secondary winding carrier drive circuit is as follows: Figure 2 As shown, each IC module is controlled by an optocoupler to isolate the on / off state of the field-effect transistor. It has 6 connection pins, of which pins 1 and 2 are the input anode and input cathode of the optocoupler in the IC module, pins 3 and 4 are the bias voltage and negative bias power supply of the field-effect transistor in the IC module, and pins 5 and 6 are the two output connection terminals of the field-effect transistor in the IC module. After connecting pins 5 of the upper transistors IC1 and IC2 in the bridge, connect them to the positive terminal of the filter capacitor C and the DC cathode of the power rectifier bridge Q. After connecting pins 4 and 6 of the upper transistor IC1, connect pin 5 of the lower transistor IC3, the B terminal of the secondary winding, and the negative terminal of the second isolation DC power supply V2. The positive terminal of the second isolation DC power supply V2 is connected to pin 3 of the upper transistor IC1. After connecting pins 4 and 6 of the upper transistor IC2, connect pin 5 of the lower transistor IC4, the A terminal of the secondary winding, and the negative terminal of the third isolation DC power supply V3. The positive terminal of the third isolation DC power supply V3 is connected to pin 3 of the upper transistor IC2. After connecting pins 6 of the lower transistors IC3 and IC4, connect resistor R4 in series to the filter capacitor. The negative terminal of C is connected to the DC positive terminal of Q in the power rectifier bridge; pins 4 of IC3 and IC4 of the lower bridge are connected to ground; pins 3 of IC3 and IC4 of the lower bridge are connected to the carrier amplitude signal output terminal (F1) of the secondary winding carrier amplitude circuit; pins 1 of IC1 and IC2 of the upper bridge are respectively connected to the output terminals of two different carrier direction signals of the secondary winding carrier direction signal circuit; pin 2 of IC1 of the upper bridge is connected to pin 1 of IC4 of the lower bridge, and pin 2 of IC2 of the upper bridge is connected to pin 1 of IC3 of the lower bridge; pins 2 of IC4 and IC3 of the lower bridge are respectively connected to the return terminals of two different carrier direction signals of the secondary winding carrier direction signal circuit. The low-voltage DC voltage V0 (which can be set to 0.65V) is output to the DC anode of the power supply rectifier bridge Q and the DC anode of the rectifier in the secondary winding carrier amplitude circuit to compensate for the potential difference.

[0034] In this structure, the bridge circuit consisting of pins 5 and 6 of the upper transistors IC1, IC2, IC3, and IC4 forms the drive circuit for the secondary winding. The DC power supply (carrier voltage) is rectified by the bridge circuit Q and filtered by the capacitor C. When the carrier direction signal turns on the upper transistors IC1 and IC4, current flows from the positive terminal of C through pin 5 of the upper transistor IC1 and out through pin 6, from end B of the secondary winding to end A, then into pin 5 of the lower transistor IC4, and finally out through pin 6 of the lower transistor IC4. The current flows out from pin 5 of the upper transistor IC2 and then back to the negative terminal of C through R4. When the carrier direction signal turns on the upper transistor IC2 and the lower transistor IC3 of the bridge, the current enters from the positive terminal of C through pin 5 of the upper transistor IC2 and exits from pin 6. It flows from terminal A to terminal B of the secondary winding, then enters pin 5 of the lower transistor IC3 and exits from pin 6 of the lower transistor IC3, before flowing back to the negative terminal of C through R4. Thus, a voltage signal V representing the magnitude of the secondary winding current is formed across R4. i In order to offset V i The potential difference between the base potential and the ground wire is used to connect the negative terminal of C to the 0.65V power supply. Since as long as the bias voltage of the lower bridge transistor IC3 and IC4 is interrupted, no current flows through the secondary winding regardless of whether the bias voltage of the upper bridge transistor IC1 and IC2 is interrupted, this invention directly uses their respective 12V isolated power supplies (V2 and V3) for the bias voltage input of the upper bridge transistor IC1 and IC2. After the bias voltage input terminals of the lower bridge transistor IC3 and IC4 are connected in parallel, the digital signal F1 of the carrier amplitude is directly input.

[0035] In an IC module, the bias voltage between 0 and 5V is the amplification region of a field-effect transistor (FET). During operation, the FET generates a significant amount of heat and must quickly pass through this region. However, the sub-phase carrier direction switches of this invention all require optocoupler isolation control. The optocoupler's power-on and power-off cycles prolong the FET's operating time in the amplification region. Therefore, this invention incorporates a voltage gate circuit between the optocoupler OC and the gate (G) of the FET in the IC module. This gate increases the bias voltage directly applied to the FET's gate to above 8V, thus bypassing the amplification region.

[0036] The specific circuit structure of the IC module is as follows: Figure 2As shown, the IC includes an optocoupler OC, a field-effect transistor (FET) M, a diode d, a Zener diode W, a bias resistor r1, a trigger resistor r2, and transistors b1, b2, b3, b4, and b5. The drain of FET M is led out from pin 5 of the IC, and the source of FET M is led out from pin 6 of the IC. The gate of FET M is connected to the emitters of transistors b3 and b4. The bases of transistors b3 and b4 are connected to the collector of transistor b5, the anode of diode d, and the emitter of transistor b2. The collector of transistor b4 is connected to the base of transistor b5, and the emitter of transistor b5 is connected to pin 4 of the IC module. The collector of transistor b3 is connected to the bias power supply of FET M. The base of transistor b2 is connected to the collector of transistor b1, and the emitter of transistor b1 is simultaneously connected to the optocoupler OC. The emitter of transistor B2, the cathode of diode D, and one end of bias resistor R1 are connected. The other end of bias resistor R1 is grounded. The collector of transistor B2 is connected to both the base of transistor B1 and the cathode of Zener diode W. The anode of W is connected in series with trigger resistor R2 and then to pin 4 of IC module. The collector of optocoupler OC is connected to pin 3 of IC module. The positive terminal of the bias power supply of MOSFET M is input from pin 3 of IC module, and the negative terminal of the bias power supply of MOSFET M is connected to pin 4 of IC module. The anode of diode in optocoupler OC is connected to pin 1 of IC module, and the cathode of diode in optocoupler OC is connected to pin 2 of IC module.

[0037] In this structure, b1, b2, b3, W, and trigger resistor r2 form a gate circuit that controls the voltage, preventing voltages below 6V from being applied to the gate of the MOSFET and preventing power loss due to insufficient bias. Meanwhile, b4, b5, diode d, and bias resistor r1 form a fast reset circuit. During the period when the carrier direction signal turns off the optocoupler, due to the inherent capacitance of the MOSFET gate, this fast reset circuit can bring the MOSFET gate potential to zero at the moment of power-off, minimizing the MOSFET's inherent power loss.

[0038] Sub-winding carrier direction signal circuit, such as Figure 1As shown, it includes a rectifier bridge Q1, a phase-shifting capacitor C1, a filter capacitor C2, a delay capacitor C3, a delay capacitor C4, a current-limiting resistor R1, a current-limiting resistor R2, a current-limiting resistor R3, a Zener diode W1, a Zener diode W2, a delay switch BG1, a delay switch BG2, a rectifier diode D1, and a rectifier diode D2. The AC terminal of rectifier bridge Q1 is connected in series with phase-shifting capacitor C1 and then connected to the two ends of AC power supply AC. The cathode of rectifier bridge Q1 is connected in series with current-limiting resistor R1, serving as the common output terminal for two different carrier direction signals of the secondary winding carrier direction signal circuit, and connected to pin 1 of the upper transistor IC1 and pin 1 of the upper transistor IC2 in the secondary winding carrier drive circuit. The DC cathode and DC anode of rectifier bridge Q1 are connected in parallel with the positive and negative terminals of filter capacitor C2, respectively, serving as the positive terminal of DC power supply DC and isolation ground wire. The cathode of rectifier diode D1 is connected to one AC terminal of rectifier bridge Q1, and the cathode of rectifier diode D2 is connected to the other AC terminal of rectifier bridge Q1. The cathode of rectifier diode D1 is also connected to one end of current-limiting resistor R2. The other end of current-limiting resistor R2 is connected to the cathode of Zener diode W1, the anode of rectifier diode D1, and one end of delay capacitor C3. The other end of container C3 is connected to the isolation ground of DC power supply DC; the cathode of rectifier diode D2 is connected to one end of current limiting resistor R3, the other end of current limiting resistor R3 is connected to the cathode of Zener diode W2, the anode of rectifier diode D2 and one end of delay capacitor C4, the other end of delay capacitor C4 is connected to the isolation ground of DC power supply DC; the anode of Zener diode W1 is connected to the base of delay switch BG1, and the anode of Zener diode W2 is connected to the base of delay switch BG2; the emitters of delay switch BG1 and delay switch BG2 are connected to the isolation ground of DC power supply DC; the collectors of delay switch BG1 and delay switch BG2 serve as the return terminals of two different carrier direction signals of the secondary winding carrier direction signal circuit, respectively, and are connected to pin 2 of the lower bridge transistor IC4 and pin 2 of the lower bridge transistor IC3 in the secondary winding carrier drive circuit.

[0039] This structure, through Q1 and C2, not only forms a rectified and filtered DC power supply, but also serves as a gate circuit for controlling the amplitude. When the voltage at the two AC terminals of Q1 is lower than the gate voltage of C2, the impedance at the two AC terminals of Q1 is extremely high, and the voltage rises rapidly; when the voltage at the two AC terminals of Q1 is higher than the gate voltage of C2, the current through Q1 is consumed by the load of the DC power supply, and the two AC terminals of Q1 are loaded with a square wave voltage. C3, C4, R2, ... R3, W1, W2, D1, D2, BG1, and BG2 constitute a delay circuit for the carrier direction signal output. When Q1 changes voltage direction from the end connected to R3 to the end connected to R2, D2 will immediately discharge the capacitor C4. The current from the rapidly increasing voltage at the R2 end of Q1 will charge C3 through R2, causing the voltage across C3 to rise slowly. When the voltage across C3 rises to the gate voltage set by W1, BG1 turns on, driving the upper transistor IC1 and the lower transistor IC4 of the bridge. Similarly, when Q1 changes voltage direction from the end connected to R2 to the end connected to R3... When the voltage direction changes, D1 immediately discharges the capacitance of C3. The current from the rapidly increasing voltage at R3 of Q1 charges C4 through R3, causing the voltage across C4 to rise more slowly. When the voltage across C4 reaches the gate voltage set by W2, BG2 turns on, driving the upper transistor IC2 and the lower transistor IC3 of the bridge. This delays the turn-on time of the optocoupler, by a length approximately greater than the turn-off delay, thus completely preventing a short circuit caused by the simultaneous turn-on of one path of the upper transistor IC1 and the other of the upper transistor IC2. R1 is the current-limiting resistor for the diode drive in the optocoupler. The MOSFET circuits in the upper transistors IC1 and IC2 of the bridge can also be replaced by thyristor circuits.

[0040] The specific circuit structure of the secondary winding carrier amplitude circuit is as follows: Figure 3 As shown, the circuit includes a rectifier bridge Q2, a phase-shifting capacitor C5, a trigger capacitor C6, a timing charging capacitor C7, a time-delay discharge capacitor C8, a bias current resistor R5, a bias current resistor R6, a reset bias current resistor R7, an amplitude adjustment resistor R8, an amplitude adjustment resistor R9, and a time-delay discharge resistor R1. 10 Current limiting resistor R 11 1. Switching transistor BG3, Reverse switching transistor BG4, Switching transistor BG5, Reset transistor BG6, Amplitude adjustment transistor BG7, Bias switching transistor BG8, Current comparison switching transistor BG9, Thyristor shutdown transistor BG 10The circuit consists of a reset diode D3, a trigger diode D4, an overload protection diode D5, and a thyristor K. The AC terminal of rectifier bridge Q2 is connected in series with a phase-shifting capacitor C5 and then connected to the two ends of the current induction coil H of the main winding. The DC anode of rectifier bridge Q2 is connected to a low-voltage DC voltage V0 (which can be set to 0.65V). Amplitude adjustment resistors R8 and R9 are connected in series, with one end connected to the DC cathode of rectifier bridge Q2 and the other end grounded. The collector of amplitude adjustment transistor BG7 is connected to the DC cathode of rectifier bridge Q2, and the emitter of amplitude adjustment transistor BG7 is connected to the DC... The base of amplitude regulating transistor BG7, connected in series with bias resistor R6 and timing charging resistor R6, is then connected to the first isolated DC power supply V1. The connection point between bias resistor R5 and bias resistor R6 is connected to the emitter of reverse switching transistor BG4 and the collector of switching transistor BG5. The emitter of switching transistor BG5 is connected to the emitter of reset transistor BG6 and one end of timing charging capacitor C7. The other end of timing charging capacitor C7 is connected to the DC anode of rectifier bridge Q2. The collector of transistor BG6 is connected to the DC anode of rectifier bridge Q2. The base of reset transistor BG6 is connected to the collector of reverse-biased switching transistor BG4, the base of switching transistor BG5, and one end of reset bias resistor R7. The other end of reset bias resistor R7 is connected to the DC anode of rectifier bridge Q2. The base of reverse-biased switching transistor BG4 is connected to the collector of switching transistor BG3. The emitter of switching transistor BG3 is grounded, and the base of switching transistor BG3 is connected to the cathode of reset diode D3. One end of the trigger capacitor C6 is connected to the DC cathode of the rectifier bridge Q2, and the anode of the reset diode D3 is grounded. The emitter of the bias switching transistor BG8 is connected to the first isolated DC power supply V1, and the collector of the bias switching transistor BG8 serves as the carrier amplitude signal output terminal (F1) of the secondary winding carrier amplitude circuit. The base of the bias switching transistor BG8 is connected to the anode of the thyristor K, and the cathode of the thyristor K is connected in parallel to the time-delay discharge capacitor C8 and the time-delay discharge resistor R. 10 After grounding, the cathode of the thyristor K is also connected to the thyristor shutdown transistor BG. 10 The collector of the thyristor K is connected to the cathode of the trigger diode D4, and the anode of the trigger diode D4 is connected to the DC cathode of the rectifier bridge Q2; the thyristor turns off transistor BG. 10 The emitter is connected to the first isolated DC power supply V1, and the thyristor shuts down the transistor BG. 10 The base is connected to the current-limiting resistor R. 11The collector of the current comparison switching transistor BG9 is connected to the collector of the current comparison switching transistor BG9. The emitter of the current comparison switching transistor BG9 is connected to the series junction of the amplitude adjustment resistor R8 and the amplitude adjustment resistor R9. The base of BG9 is connected to pin 6 of the lower transistor IC3 and the lower transistor IC4 in the secondary winding carrier drive circuit. The series junction of the amplitude adjustment resistor R8 and the amplitude adjustment resistor R9 is also connected to the anode of the overload protection diode D5. The cathode of the overload protection diode D5 is grounded.

[0041] With this structure, the main phase current signal induced by H is phase-shifted by C5 and rectified by Q2 to obtain a unidirectional wave current signal of phase-shifted carrier signal. When the shunt switch is not open, 1 / 3 of the current flows back through R8 and R9, and 2 / 3 of the current flows back through the collector of BG7 to the emitter. The stored energy in C7 flows from the emitter of BG6 to the base, and then forms a bias current circuit through R7. When BG6 is opened, it discharges and resets instantly. C6 is reset through D3, and the collector of BG7 outputs the voltage amplitude of the sinusoidal potential drop phase. BG3, BG4, BG5, D3, and C6 constitute the aforementioned up / down switch. During the rising phase of the unidirectional wave potential of the phase-shifted carrier signal, the potential across C6 also continuously rises. Current continuously flows through C6 and then turns on the up / down switch from the base of BG3. The current through R5 flows back through C7 at the moment of opening, and the current in BG7 is cut off. As the potential across C7 increases, the current in BG7 recovers synchronously with the voltage across C7, and the voltage amplitude at the collector of BG7 is corrected to become the sinusoidal amplitude output during the rising phase.

[0042] The core innovation of the capacitor phase-shifting motor system circuit of this invention lies in extracting voltage across the current sensing coil H of the main winding using a carrier amplitude circuit in the secondary winding. Specifically, it extracts the current signal from the main winding circuit through the main winding current detection coil H, and after phase-shifting and rectification of the main winding current signal, corrects the amplitude of the secondary phase voltage signal by adjusting the magnitude of the secondary phase voltage signal current through the opening of the resistor and capacitor circuits. The amplitude potential of the secondary phase voltage wave at different stages is compared with the potential of the current signal when the secondary winding is energized to synchronously control the current input of the secondary winding. Furthermore, the amplitude potential of the secondary phase voltage wave at different stages is compared with the potential of the resistor and capacitor delay discharge circuit to synchronously obtain the interruption delay time of the secondary phase current. The phase shift of the power supply voltage is used to restore the direction of the secondary phase voltage loading into the secondary winding. The secondary winding ultimately obtains a digital wave drive power supply whose input magnitude is controlled by the main phase input current. Thus, since the main winding is directly driven by the power supply, the current in the electronic circuit is halved, effectively solving the interference problem of the bridge rectifier filter circuit on the power supply, and improving the motor torque and efficiency.

[0043] Specifically, the secondary winding carrier amplitude circuit extracts the current signal from the main winding circuit through the main winding current detection coil H. After phase shifting by the capacitor C5, it is rectified into a half-wave signal using the bridge Q2. The capacitor C6 further distinguishes the potential change state of the half-wave signal. During the rising phase of the half-wave signal, the current through the capacitor C6 turns on the transistors BG3, BG4, and BG5. The charging current of the capacitor C7 shuns part of the current in the resistor R5, causing the bias current of the transistor BG7 to decrease proportionally. This reduces the current in the half-wave signal circuit by a factor of two, thereby increasing the voltage drop of the half-wave signal to ground during the rising phase. As a result, the amplitude of the half-wave signal during the rising phase is increased according to the amplitude change curve of the delayed charging of the resistor R5 and the capacitor C7.

[0044] After receiving the analog wave of the secondary winding carrier signal, this invention uses the analog wave potential of the secondary winding carrier signal to trigger the thyristor K through D4. The thyristor K turns on one of the lower transistors IC3 or IC4 of the secondary winding drive bridge through BG8. When the secondary phase current passes through the step-down resistor R4, a current signal voltage (F2) is generated at the current output terminal of the lower transistor of the secondary winding drive bridge. This current signal voltage (F2) is compared with the base input of the switching transistor BG9 and the carrier signal potential after stepping down through R8 and R9 at the emitter of BG9 to obtain the first potential loading. When the base potential of BG9 is greater than its emitter potential by 0.65V, the collector and emitter of BG9 conduct, and BG... 10 When the base follower is turned on, the current from power supply V1 to the thyristor cathode flows through BG, which has a smaller nonlinear impedance. 10 When the thyristor cathode is reached, BG8 and the thyristor current are cut off. At this time, the secondary winding drive current is still in the delayed conduction state caused by the field-effect transistor. When the secondary winding drive current is cut off, BG9 and BG... 10 Current follows the cutoff, and the secondary winding drive enters 0 potential operation; C8 then passes through R 10 The discharge starts with a delay from the peak potential. When the potential across C8 drops to 1.2V below the secondary winding carrier signal potential, the analog wave potential of the secondary winding carrier signal triggers the thyristor to conduct through D4.

[0045] The amplitude potential of the secondary phase voltage wave at different stages is compared with the current signal potential of the secondary winding. This is achieved by obtaining the secondary winding current signal through the step-down resistor R4 in the secondary phase DC circuit, which is then input to the base terminal of transistor BG9. The emitter terminal of transistor BG9 is connected to the half-wave signal output terminal with amplitude voltage matching. The collector of transistor BG9 is connected to the base terminal of transistor BG9 through resistor R5. 10 The base terminal of the transistor BG 10The emitter terminal is connected to the voltage V1 terminal, and the transistor BG 10 The collector terminal of the capacitor C7 is connected to the resistor R. 10 The delayed discharge voltage terminal is formed; the voltage V0 is different from the ground by the PN junction voltage drop between the base and emitter of the transistor BG9; thus, when the secondary winding current signal potential exceeds the half-wave signal potential of the amplitude voltage matching, the transistor BG9... 10 The emitter and collector are connected, due to the transistor BG 10 The voltage drop from the emitter to the collector is 0.3V, while the voltage drop from the emitter of transistor BG8 to the cathode of the thyristor K is 1.6V. Therefore, in transistor BG... 10 When the emitter and collector are connected, the current from the emitter of the transistor BG8 to the cathode of the thyristor K will be cut off, and the collector of the transistor BG8 will output a 0 signal.

[0046] The amplitude potential of the subphase voltage wave at different stages is related to the resistance R. 10 Compared to the potential of the delayed discharge circuit formed by capacitor C8, the half-wave signal is connected to the trigger electrode of the thyristor through trigger diode D4. When the collector of transistor BG8 outputs a 0 signal, the secondary winding current will drop to zero, and the transistor BG... 10 When the current from the emitter to the collector is cut off, the capacitor C8 begins to flow through the resistor R. 10 When the voltage across capacitor C8 drops below the half-wave signal potential, triggering the thyristor K, the emitter-collector junction of transistor BG8 is turned on, and the collector of transistor BG8 outputs a 1 signal.

[0047] The voltage of the power supply AC is phase-shifted by the capacitor C8, shifting the time of the carrier voltage direction change by 90°, and outputting a sub-phase carrier direction voltage. This sub-phase carrier direction voltage is rectified by the bridge Q1 and filtered by the capacitor C2 before outputting current. At the two AC terminals of the bridge Q1, a low-potential square wave signal voltage controlling the sub-phase carrier direction is obtained. When the square wave signal voltage direction is the same as the base bias current loading direction of the transistor BG1, the capacitor C4 is immediately reset through the fast recovery diode D2, and the collector and emitter of the transistor BG2 are immediately disconnected. The IC2 and IC3 on the positive carrier side are turned off. Simultaneously, the square wave signal current charges the capacitor C3 through the resistor R2 with current limiting. When the voltage across the capacitor C3 reaches the current generated by the Zener diode W1, the collector and emitter of the transistor BG1 are delayed and turned on, and the IC1 and IC4 on the reverse carrier side are simultaneously turned on. When the voltage direction is the same as the base bias current loading direction of the transistor BG2, the capacitor C3 is immediately reset through the fast recovery diode D1, the collector and emitter of the transistor BG1 are immediately disconnected, and IC1 and IC4 on the reverse carrier side are turned off. At the same time, the square wave signal current charges the capacitor C4 through the resistor R3 with current limiting. When the voltage across the capacitor C4 reaches the current generated by the Zener diode W2, the collector and emitter of the transistor BG2 are turned on after a delay, and IC2 and IC3 on the positive carrier side are turned on simultaneously; thus, the carrier direction of the secondary winding is restored. It should be noted that only one of the two circuits on the forward carrier side (IC2 and IC3) and the reverse carrier side (IC1 and IC4) will be turned on at a time; they will not be turned on simultaneously, as doing so would burn out the MOSFETs. Furthermore, the optocoupler has a delay of several microseconds during switching, and there must be a delay when the sub-phase switches the carrier direction, so delay processing is required in the circuit.

[0048] An example circuit of a switching power supply is as follows: Figure 4 As shown, it includes transformer E05, capacitor C9, and capacitor C. 10 Capacitor C 11 Capacitor C 12 Capacitor C 13 Resistance R 12 Resistance R 13 Resistance R 14 Zener diode W3, transistor BG 11 Transistor BG 12 Transistor BG 13Diodes D6, D7, D8, and D9 are used. Transformer E05 includes two primary coils and three secondary coils: a first primary coil, a second primary coil, a first secondary coil, a second secondary coil, and a third secondary coil. One end of the first primary coil is connected to the positive terminal of the DC power supply, and the other end is connected to transistor BG. 11 The collector of the transistor BG 11 The emitter of the transistor is connected to the isolated ground of the DC power supply, and the transistor BG... 11 Base connection resistor R 12 One end of the resistor is connected to the cathode of the Zener diode W3, and the resistor R is connected to the cathode of the Zener diode W3. 12 The other end is connected to the positive terminal of the DC power supply, and the anode of the Zener diode W3 is connected to the capacitor C. 10 The negative terminal of diode D6 is connected to the anode of diode D6, and the cathode of diode D6 is connected to one end of the second primary coil. The other end of the second primary coil is connected to capacitor C. 10 The positive terminals of all components are connected to the isolated ground wire of the DC power supply; resistor R 13 After being connected in series with capacitor C9, one end is connected to transistor BG. 11 The base of the diode is connected to the cathode of diode D6 at the other end; the secondary coil is connected in series with diode D8 and then with capacitor C. 12 The two ends of the parallel connection serve as the positive and negative terminals of the second isolation DC power supply V2; the third stage coil is connected in series with diode D9 and then with capacitor C. 13 The two ends of the parallel connection serve as the positive and negative terminals of the third isolation DC power supply V3; the first stage coil is connected in series with diode D7 and capacitor C. 11 Connected in parallel, the two ends of the parallel connection serve as the positive terminal and ground terminal of the first isolation DC power supply V1; transistor BG 13 The emitter of transistor BG is connected to the ground terminal of the first isolation DC power supply V1. 13 The collector of the transistor BG is connected. 12 The base and resistor R 14 One end, resistor R 14 The other end and transistor BG 12 The collectors of transistors BG are all connected to the positive terminal of the first isolated DC power supply V1. 12 emitter and transistor BG 13 After being connected to the base, it serves as the output terminal of the low-voltage DC voltage V0.

[0049] The input voltage (DC) of the switching power supply circuit is set at approximately 5V to match the square wave generation of the carrier direction signal. It has three isolated power supply outputs: V1, V2, and V3. V2 and V3 respectively provide bias voltage to the two upper transistors (pin 3 of the bridge upper transistors IC1 and IC2) for starting the secondary winding. V1 is used by the secondary winding carrier amplitude circuit. V1 also passes through BG12 and BG... 13 and R 14 Obtaining a 0.65V power output is primarily to eliminate the PN junction voltage drop from the base to the emitter of the BG9 transistor and to reduce the PN junction voltage drop at the trigger electrode of the thyristor. In practical applications, other commonly used simple switching power supplies can also be used instead of the switching power supply circuit.

[0050] The design concept and working principle of the capacitor phase-shifting motor system circuit of the present invention will be summarized and explained below.

[0051] In a capacitor-phase-shifting motor system, during the auxiliary winding's assisted excitation of the main winding, when the main phase potential is between 0° and 90°, the magnetic flux direction of the main phase excitation leads the magnetic flux direction locked by the rotor electrodes. This lead distance allows for the stator to output torque to the rotor. However, from 90° to 180°, as the rotor rotates with its internal magnetic flux, the magnetic flux direction of the main phase excitation lags behind the magnetic flux direction locked by the rotor electrodes, and the main winding enters a standby state. If the main winding needs to generate torque to the rotor during this period, the current input to the auxiliary winding must be based on a sinusoidal amplitude to maintain the lead of the stator magnetic flux direction over the rotor magnetic flux direction; otherwise, the current input to the stator by the main winding during this period will be wasted.

[0052] Therefore, in specific applications, the capacitor phase-shifting motor system circuit of the present invention can be designed to drive the auxiliary winding using digital wave drive; the main winding can be directly driven by the power supply, and the main winding wiring preferably uses the stator winding winding method in the "A wiring structure and working method of a capacitor motor winding" (patent number CN2020101769308) previously disclosed by the inventor. It uses the electromagnetic induction of the auxiliary winding to reorganize the electrodes of the main winding, and can reorganize the electrodes of the main winding to their respective phase positions at the 60°, 90° and 120° phase periods of the main phase, so that the two-phase motor can achieve the output torque of a three-phase motor. Furthermore, the heat dissipation and cost of electronic components can be reduced to less than 1 / 3 of those of comparable frequency converters. After the torque output of the main phase of the motor increases during the 60° and 120° phase periods, the increased current at the end complements the current consumption of the secondary phase during the peak period, forming a sinusoidal current consumption overall, thus solving the interference problem of the rectifier filter circuit on the power supply. Moreover, when the motor starts, only the maximum excitation current at the secondary winding distribution phase is limited, while the main winding is driven by changing the electrode arrangement within a 30° phase before and after the distribution, and the maximum excitation current is not limited.

[0053] Since the secondary winding assists the main winding in excitation operation, the amplitude of the secondary phase voltage needs to be proportional to the main phase torque output during the main phase potential rise period and inversely proportional to the main phase torque output during the main phase potential fall period. This effect can be achieved by using the main phase current signal to phase-shift through a capacitor. During the main phase potential rise period, the main phase voltage direction is the same as the secondary phase voltage direction. The greater the main phase torque output, the higher the main phase current signal amplitude, and the higher the phase-shifted voltage amplitude. Conversely, during the main phase potential fall period, the main phase voltage direction is opposite to the secondary phase voltage direction. During this period, the lower the main phase torque output, the lower the main phase current signal amplitude, and the phase-shifted voltage amplitude will increase proportionally.

[0054] While using the main phase current signal to phase-shift via a capacitor can partially solve the problem of the low amplitude of the secondary phase in the 0° to 45° range, it still fails to adjust this amplitude to the standard sine wave. However, in the capacitor phase-shifting circuit, the phase-shifting voltage is a voltage divider formed across the load in a series circuit consisting of the AC power supply, the capacitor, and the load current. The amplitude potential of the phase-shifting voltage is proportional to the load impedance. Therefore, by adjusting the load resistance value at different times, the amplitude potential of the phase-shifting voltage can be adjusted synchronously, solving the problem of the low amplitude potential of the secondary phase voltage during its unidirectional wave potential rise, and achieving the standard of secondary winding assisting main winding excitation.

[0055] Therefore, this invention utilizes the characteristic that the input terminal of a switching power supply is a voltage gate circuit. The bridge rectifier and filter circuit of the switching power supply is used as the load circuit for the phase-shifted voltage. The two AC terminals of the bridge are the output signal terminals of the phase-shifted voltage. When the voltage at the two AC input terminals of the switching power supply does not reach the DC terminal voltage of the bridge, the phase-shifted load impedance is extremely high, instantly raising the voltage across the load to the voltage across the filter capacitor. Immediately, a current equal to the current flowing through the phase-shifting capacitor is generated. A portion of this current is supplied to the optocoupler and the switching power supply, while the excess current is stored in the filter capacitor. In this way, the signal controlling the carrier direction of the secondary winding becomes a square wave signal, which can control the output of the optocoupler in both forward and reverse directions. Additionally, a capacitor delay-on device needs to be added to each diode circuit terminal of the optocoupler, with a delay time greater than the optocoupler's response time. This prevents the field-effect transistor from burning out when the forward and reverse control switches are turned on simultaneously.

[0056] The amplitude voltage signal of the secondary winding carrier is obtained by phase shifting the current-induced wave of the main winding through a capacitor and then rectifying it into a unidirectional wave signal through a bridge circuit. When setting the load circuit of the phase shifting circuit, a small portion of the current flows back through a resistor, and most of the current flows back through a transistor. During the phase of carrier potential decline, the carrier signal potential increase / decrease switch (referred to as the increase / decrease switch) is turned on. The bias current of the transistor is used to charge the timing capacitor, thereby shunting the bias current of the transistor and increasing the load impedance. The amplitude of the phase shift voltage potential rise phase changes according to the amplitude of the voltage across the timing capacitor.

[0057] The specific implementation involves first connecting a resistor from the signal terminal to ground to control the peak of the secondary winding carrier signal voltage at the same potential as the V1 power supply. Then, the collector of a transistor is connected to the signal terminal, the emitter is grounded, and the base is connected to a bias current supply to one end of a charging timing resistor. The other end of the charging timing resistor is connected to the V1 power supply. The series connection point of the bias current resistor and the timing resistor is connected to a shunt switch to one end of a timing capacitor, and the other end of the timing capacitor is grounded. The charging time for the timing capacitor to go from zero to the peak is 1 / 4f seconds. One end of a trigger capacitor is connected to the control terminal of the timing charging switch, and the other end is connected to the signal terminal of the secondary winding carrier voltage. Therefore, during the rising phase of the secondary winding carrier signal voltage, the voltage across the trigger capacitor continuously rises, activating the increment / decrement switch to charge the timing capacitor. The bias current of the transistor is shunt by the timing capacitor, and the amplitude of the carrier voltage rises synchronously with the potential across the timing capacitor. During the falling phase of the secondary winding carrier signal voltage, the trigger capacitor cannot activate the increment / decrement switch, and the phase-shifting voltage alternates in amplitude according to the fixed resistor load.

[0058] Even with the analog wave of the secondary winding carrier signal, it is still insufficient to directly drive the field-effect transistor (FET); a digital wave is also required to drive the FET. Therefore, this invention uses the analog wave potential of the secondary winding carrier signal to trigger the thyristor. The anode of the thyristor is connected to the control terminal of the FET bias switch, and the cathode is connected to the positive terminal of the delay discharge capacitor. Simultaneously, the stepped-down secondary winding carrier signal voltage is applied to the emitter voltage of the current comparison switch transistor. The base of the current comparison switch transistor receives the corresponding secondary winding current signal voltage, and the collector of the current comparison switch transistor is connected to the control terminal of the thyristor's turn-off switch. Therefore, when the potential of the secondary winding carrier signal is higher than the potential across the delay discharge capacitor at the same moment, the thyristor is triggered and turns on, the bias voltage of the field-effect transistor (FET) is turned on, and the FET is in the 1-potential operation stage. When the potential of the feedback secondary winding current signal is higher than the potential of the reduced secondary winding carrier signal at the same moment, the current comparison switch opens the thyristor off switch, the thyristor current is immediately cut off, and the bias voltage of the FET is turned off, the secondary winding current is cut off, and the FET is in the 0-potential operation stage. When the potential across the delay capacitor drops from the peak potential at the time of power-off to below the potential of the carrier signal at the same moment, the thyristor is triggered and turns on again, entering the 1-potential operation period. Thus, during the 1-potential operation period, the higher the amplitude potential of the carrier signal, the greater the current flowing through the secondary winding; while during the 0-potential operation period, the higher the amplitude potential of the carrier signal, the shorter the 0-potential operation time; the current carrier through the secondary winding is precisely controlled as a digital sine wave.

[0059] The specific implementation involves using an analog wave of the secondary winding carrier signal to trigger the thyristor via a trigger diode. A time-delay discharge resistor and a time-delay discharge capacitor are connected to ground at the thyristor cathode. The thyristor anode is connected to the base of a bias switching transistor, and the collector of a bias switching transistor is connected to a 12V DC power supply. The emitter of the bias switching transistor is the bias power supply terminal for the two lower transistors of the secondary winding drive bridge. A step-down resistor is then connected to the source circuit of the lower transistor in the secondary winding drive bridge to extract the voltage signal of the secondary winding drive current. This signal is then connected to the base of a current comparison switching transistor. The emitter of the current comparison switching transistor is connected to the stepped-down secondary winding carrier signal voltage. The collector of the current comparison switching transistor is connected to the base of the thyristor shutdown transistor via a current-limiting resistor. The collector of the thyristor shutdown transistor is connected to a 12V DC power supply, and the emitter of the thyristor shutdown transistor is connected to the thyristor cathode. With this structure, the thyristor is triggered to conduct when its cathode potential is less than its trigger electrode potential by 0.65V. At V1=12V, the thyristor cathode potential reaches 10.4V, and the thyristor anode potential is 11.35V, thus turning on the secondary winding drive circuit. The voltage signal converted from the current is then applied to the base of the current comparison switching transistor. When its base potential is 0.65V higher than the secondary winding carrier signal potential at its emitter by 0.65V, both the bias switching transistor and the thyristor shut-off transistor simultaneously conduct. At this point, the thyristor cathode... The potential becomes 11.7V, higher than the 11.35V of the thyristor anode. The thyristor current is turned off, and the bias switching transistor, the thyristor turn-off transistor, and the current comparison switching transistor are simultaneously turned off. The time-delay discharge capacitor begins to discharge through the time-delay discharge resistor. The thyristor cathode potential decreases as the time-delay discharge time increases. When the thyristor cathode potential drops from 11.7V to 1.2V lower than the secondary winding carrier signal potential at the same time, the thyristor is triggered to conduct again, repeating the previous process. In this way, by dynamically controlling the magnitude of the secondary winding current, it perfectly corresponds to the synchronous change of the secondary winding carrier signal potential. The interruption time is longer when the secondary winding carrier signal potential is lower and shorter when the secondary winding carrier signal potential is higher, which fully conforms to the interruption concept of variable frequency motors.

[0060] As can be seen, compared with the prior art, the present invention has the following advantages: 1. The capacitor phase-shifting motor system circuit of this invention achieves electrode rearrangement of the main winding at 60°, 90°, and 120° phase periods through a collaborative design of digital wave drive for the auxiliary winding and direct power supply drive for the main winding, combined with the patented "capacitor motor winding wiring structure" technology. This design enables a two-phase motor to achieve the output torque level of a three-phase motor. Simultaneously, through the complementary effect of the main phase current and auxiliary phase current, a sinusoidal current consumption is formed, significantly reducing the interference of the rectifier filter circuit on the power supply. After the increased torque output of the motor at 60° and 120° phase periods, the terminal current and the auxiliary phase peak current consumption complement each other, improving overall efficiency and reducing heat dissipation and component costs to less than 1 / 3 of comparable frequency converters.

[0061] 2. In the capacitor-phase-shifted motor system circuit of this invention, during motor startup, the auxiliary winding is only limited by the maximum excitation current at certain phases, while the main winding achieves current-free drive within a 30° phase range through electrode arrangement adjustment, ensuring easy startup and minimizing component damage. The amplitude of the auxiliary phase voltage is dynamically adjusted via capacitor phase shifting using the main phase current signal: when the main phase potential rises, the auxiliary phase voltage moves in the same direction as the main phase, resulting in a higher torque output and a higher phase-shifted voltage amplitude; conversely, when the main phase potential falls, the auxiliary phase voltage reverses, resulting in a lower torque output and a higher phase-shifted voltage amplitude. This design effectively solves the problem of insufficient amplitude in the auxiliary phase from 0° to 45°, and simultaneously ensures the standard compliance of the auxiliary winding's auxiliary excitation of the main winding through dynamic adjustment of the load impedance.

[0062] 3. The capacitor phase-shifting motor system circuit of this invention uses a switching power supply bridge rectifier and filter circuit as the phase-shifting voltage load circuit. Utilizing its voltage gate circuit characteristics, when the AC input voltage is below the DC input voltage, the load impedance is extremely high, allowing for an instantaneous boost of the load voltage to the filter capacitor voltage, and shunting current to the optocoupler and switching power supply. Most major electronic components can be integrated into the motor terminal block, relying on the chassis for heat dissipation. Except for the DC filter capacitor, all other electronic components can be integrated, significantly reducing circuit costs (by more than 50%). Simultaneously, by adding a capacitor delay device to the optocoupler diode circuit, damage to the MOSFET caused by simultaneous activation of forward and reverse switches is avoided, improving system reliability.

[0063] 4. In the capacitor-phase-shifting motor system circuit of this invention, the carrier signal of the secondary winding is phase-shifted by a capacitor and rectified by a bridge circuit. Then, it is driven by a digital wave through a thyristor and a current comparison switching transistor to drive the field-effect transistor. Specifically, the carrier analog wave triggers the thyristor, and combined with a delayed discharge capacitor and a current comparison mechanism, achieves precise digital sinusoidal control of the secondary winding current: when operating at potential 1, the higher the carrier amplitude, the larger the secondary winding current; when operating at potential 0, the higher the carrier amplitude, the shorter the potential 0 time. This design synchronously increases the carrier amplitude by adjusting the potential across the timing capacitor and fixes the alternating amplitude of the resistive load during the potential drop phase, ensuring that the current control accuracy conforms to the frequency converter motor interruption concept. It also solves the problem of insufficient amplitude during the secondary phase voltage rise phase, improving the overall system efficiency and stability.

[0064] In summary, the capacitor phase-shifting motor system circuit of this invention corrects the amplitude of the secondary phase voltage by adjusting the magnitude of the secondary phase voltage signal current after phase-shifting and rectifying the main winding current signal and opening the resistor and capacitor circuits. It compares the amplitude potential of the secondary phase voltage wave at different stages with the potential of the current signal when the secondary winding is energized to synchronously control the current input of the secondary winding. Furthermore, it compares the amplitude potential of the secondary phase voltage wave at different stages with the potential of the resistor and capacitor delay discharge circuit to synchronously obtain the interruption delay time of the secondary phase current. It also uses phase shifting of the power supply voltage to restore the direction of the secondary phase voltage loading into the secondary winding. Finally, the secondary winding receives a digital wave drive power supply whose input magnitude is controlled by the main phase input current. Thus, since the main winding is directly driven by the power supply, the current in the electronic circuit is halved, effectively solving the interference problem of the bridge rectifier filter circuit on the power supply and improving the motor torque and efficiency. Moreover, this invention achieves a breakthrough in performance throughout the entire cycle from startup to operation through optimized heat dissipation integration, improved control precision, and improved protection mechanisms. Its high efficiency, reliability, and low cost make it a significant technical and economic asset, and it can be widely used in motor drive scenarios that require high torque, high efficiency, and low cost, such as home appliances, industrial machinery, and automation equipment, providing new prospects for the application and promotion of capacitor phase-shifting motor technology.

[0065] Finally, it should be noted that the above embodiments are only used to illustrate the technical solutions of the present invention and not to limit the technical solutions. Those skilled in the art should understand that any modifications or equivalent substitutions to the technical solutions of the present invention without departing from the spirit and scope of the present invention should be covered within the scope of the claims of the present invention.

Claims

1. A capacitor phase-shifting motor system circuit, comprising a main winding, an auxiliary winding, and a digital wave drive power supply with a 90° phase shift, wherein the main winding is directly driven by an AC power supply, and the auxiliary winding is driven by the digital wave drive power supply with the 90° phase shift, characterized in that... The AC power supply is rectified by the power rectifier bridge Q and stepped down by the resistor R4 to form a carrier voltage. The carrier voltage is then applied to both ends of the secondary winding through the secondary winding carrier direction drive circuit to control the direction and amplitude of the carrier voltage applied to the secondary winding. The secondary winding carrier direction drive circuit includes a secondary winding carrier drive circuit, a secondary winding carrier direction signal circuit, a secondary winding carrier amplitude circuit, and a switching power supply circuit. The secondary winding carrier drive circuit includes a bridge circuit composed of four IC modules. The four IC modules are IC2 (upper bridge transistor) and IC3 (lower bridge transistor) on the forward carrier side, and IC1 (upper bridge transistor) and IC4 (lower bridge transistor) on the reverse carrier side. Each IC module is a module circuit that uses an optocoupler to isolate and control the on / off state of a field-effect transistor. The two ends of the secondary winding are designated as terminals A and B. The two output terminals of the field-effect transistor in IC2 (upper bridge transistor) on the forward carrier side are connected to the DC cathode of the power rectifier bridge Q and terminal A of the secondary winding, respectively. The two output terminals of the field-effect transistor in IC3 (lower bridge transistor) on the forward carrier side are connected to terminal B of the secondary winding and connected to the DC anode of the power rectifier bridge Q via resistor R4. The two output terminals of the field-effect transistor in IC1 (upper bridge transistor) on the reverse carrier side are connected to the DC cathode of the power rectifier bridge Q, respectively. The two output terminals of the field effect transistor in IC1 of the bridge on the reverse carrier side are connected to the A terminal of the secondary winding and the DC anode terminal of the power rectifier bridge Q through resistor R4, respectively. The input sides of the optocouplers in the two IC modules on the positive carrier side are connected in series to one of the carrier direction signal output terminals of the secondary winding carrier direction signal circuit. The input sides of the optocouplers in the two IC modules on the reverse carrier side are connected in series to the other of the carrier direction signal output terminals of the secondary winding carrier direction signal circuit. Thus, the two IC modules on the positive carrier side or the two IC modules on the reverse carrier side in the secondary winding carrier drive circuit are turned on by the different carrier direction signals of the secondary winding carrier direction signal circuit, so that the current direction formed by the carrier voltage flows from the A terminal to the B terminal of the secondary winding, or from the B terminal to the A terminal of the secondary winding. The secondary winding carrier direction signal circuit extracts voltage from the AC power supply terminals and converts it into DC power supply output to the switching power supply circuit through rectification and conversion. By phase shifting the DC power supply, two different carrier direction signals are generated and output to the secondary winding carrier drive circuit. The secondary winding carrier amplitude circuit extracts the voltage across the current sensing coil H of the main winding, and after phase shifting, rectification, and delay processing, forms a carrier amplitude signal, which is used to provide bias voltage to the field-effect transistors of the two lower bridge transistors in the secondary winding carrier drive circuit, thereby dynamically controlling the amplitude of the secondary winding input voltage and the amplitude of the input current. The switching power supply circuit is used to perform isolation voltage conversion on the DC power supply to form a first isolated DC power supply V1, a second isolated DC power supply V2, and a third isolated DC power supply V3 with a first set voltage value, and to step down the first isolated DC voltage to a low-voltage DC voltage V0 with a second set voltage value; wherein, the first isolated DC power supply V1 is output to the delay processing circuit in the secondary winding carrier amplitude circuit; the second isolated DC power supply V2 and the third isolated DC power supply V3 are respectively used to provide bias voltage to the field-effect transistors on the two bridge transistors in the secondary winding carrier drive circuit; the low-voltage DC voltage V0 is output to the DC anode of the power rectifier bridge Q and the DC anode of the rectifier in the secondary winding carrier amplitude circuit to cancel the potential difference.

2. The capacitor phase-shifting motor system circuit according to claim 1, characterized in that, Each IC module is controlled by an optocoupler to isolate the on / off state of the field-effect transistor. It has 6 connection pins, of which pins 1 and 2 are the input anode and input cathode of the optocoupler in the IC module, pins 3 and 4 are the bias voltage and negative bias power supply of the field-effect transistor in the IC module, and pins 5 and 6 are the two output connection terminals of the field-effect transistor in the IC module.

3. The capacitor phase-shifting motor system circuit according to claim 2, characterized in that, The specific circuit structure of each IC module includes an optocoupler OC, a field-effect transistor M, a diode d, a Zener diode W, a bias resistor r1, a trigger resistor r2, and transistors b1, b2, b3, b4, and b5. The drain of the field-effect transistor M is led out from pin 5 of the IC, and the source of the field-effect transistor M is led out from pin 6 of the IC. The gate of the field-effect transistor M is connected to the emitter of transistors b3 and b4. The bases of transistors b3 and b4 are connected to the collector of transistor b5, the anode of diode d, and the emitter of transistor b2. The collector of transistor b4 is connected to the base of transistor b5. The emitter of transistor b5 is connected to pin 4 of the IC module. The collector of transistor b3 is connected to the bias power supply of the field-effect transistor M. The base of transistor b2 is connected to the collector of transistor b1. The emitter of transistor b1 is simultaneously connected to optocoupler O. The emitter of transistor C, the cathode of diode d, and one end of bias resistor r1 are connected. The other end of bias resistor r1 is grounded. The collector of transistor b2 is connected to both the base of transistor b1 and the cathode of Zener diode W. The anode of W is connected in series with trigger resistor r2 and then to pin 4 of the IC module. The collector of optocoupler OC is connected to pin 3 of the IC module. The positive terminal of the bias power supply of MOSFET M is input from pin 3 of the IC module, and the negative terminal of the bias power supply of MOSFET M is connected to pin 4 of the IC module. The anode of the diode in optocoupler OC is connected to pin 1 of the IC module, and the cathode of the diode in optocoupler OC is connected to pin 2 of the IC module.

4. The capacitor phase-shifting motor system circuit according to claim 2, characterized in that, In the specific circuit structure of the secondary winding carrier drive circuit, pins 5 of the upper transistors IC1 and IC2 of the bridge are connected to the positive terminal of the filter capacitor C and the DC negative terminal of the power rectifier bridge Q; pins 4 and 6 of the upper transistor IC1 are connected to pin 5 of the lower transistor IC3, the B terminal of the secondary winding, and the negative terminal of the second isolation DC power supply V2; the positive terminal of the second isolation DC power supply V2 is connected to pin 3 of the upper transistor IC1; pins 4 and 6 of the upper transistor IC2 are connected to pin 5 of the lower transistor IC4, the A terminal of the secondary winding, and the negative terminal of the third isolation DC power supply V3; the positive terminal of the third isolation DC power supply V3 is connected to pin 3 of the upper transistor IC2; pins 6 of the lower transistors IC3 and IC4 are connected in series. Resistor R4 is connected to the negative terminal of filter capacitor C and the DC positive terminal of power rectifier bridge Q; pins 4 of lower bridge transistors IC3 and IC4 are connected to ground; pins 3 of lower bridge transistors IC3 and IC4 are connected to the carrier amplitude signal output terminal (F1) of the secondary winding carrier amplitude circuit; pins 1 of upper bridge transistors IC1 and IC2 are connected to the output terminals of two different carrier direction signals of the secondary winding carrier direction signal circuit; pin 2 of upper bridge transistor IC1 is connected to pin 1 of lower bridge transistor IC4, and pin 2 of upper bridge transistor IC2 is connected to pin 1 of lower bridge transistor IC3; pins 2 of lower bridge transistors IC4 and IC3 are connected to the return terminals of two different carrier direction signals of the secondary winding carrier direction signal circuit.

5. The capacitor phase-shifting motor system circuit according to claim 4, characterized in that, The secondary winding carrier direction signal circuit includes a rectifier bridge Q1, a phase-shifting capacitor C1, a filter capacitor C2, a delay capacitor C3, a delay capacitor C4, a current-limiting resistor R1, a current-limiting resistor R2, a current-limiting resistor R3, a Zener diode W1, a Zener diode W2, a delay switch BG1, a delay switch BG2, a rectifier diode D1, and a rectifier diode D2. The AC terminal of the rectifier bridge Q1 is connected in series with a phase-shifting capacitor C1 and then connected to the two ends of the AC power supply. The cathode of the rectifier bridge Q1 is connected in series with a current-limiting resistor R1, serving as the common output terminal for two different carrier direction signals of the secondary winding carrier direction signal circuit. The DC cathode and DC anode of the rectifier bridge Q1 are connected in parallel with the positive and negative terminals of the filter capacitor C2, respectively, serving as the positive terminal of the DC power supply and the isolation ground wire. The cathode of rectifier diode D1 is connected to one AC terminal of the rectifier bridge Q1, and the cathode of rectifier diode D2 is connected to the other AC terminal of the rectifier bridge Q1. The cathode of rectifier diode D1 is also connected to one end of the current-limiting resistor R2. The other end of the current-limiting resistor R2 is connected to the cathode of the Zener diode W1, the anode of rectifier diode D1, and one end of the delay capacitor C3. The other end of capacitor C3 is connected to the isolation ground of DC power supply DC; the cathode of rectifier diode D2 is connected to one end of current limiting resistor R3, the other end of current limiting resistor R3 is connected to the cathode of Zener diode W2, the anode of rectifier diode D2 and one end of delay capacitor C4, the other end of delay capacitor C4 is connected to the isolation ground of DC power supply DC; the anode of Zener diode W1 is connected to the base of delay switch BG1, and the anode of Zener diode W2 is connected to the base of delay switch BG2; the emitters of delay switch BG1 and delay switch BG2 are connected and then connected to the isolation ground of DC power supply DC; the collectors of delay switch BG1 and delay switch BG2 serve as the return terminals for two different carrier direction signals of the secondary winding carrier direction signal circuit.

6. The capacitor phase-shifting motor system circuit according to claim 5, characterized in that, The secondary winding carrier amplitude circuit includes a rectifier bridge Q2, a phase-shifting capacitor C5, a trigger capacitor C6, a timing charging capacitor C7, a time-delay discharge capacitor C8, a bias current resistor R5, a bias current resistor R6, a reset bias current resistor R7, an amplitude adjustment resistor R8, an amplitude adjustment resistor R9, and a time-delay discharge resistor R1. 10 Current limiting resistor R 11 1. Switching transistor BG3, Reverse switching transistor BG4, Switching transistor BG5, Reset transistor BG6, Amplitude adjustment transistor BG7, Bias switching transistor BG8, Current comparison switching transistor BG9, Thyristor shutdown transistor BG 10 1. Reset diode D3, trigger diode D4, overload protection diode D5, and thyristor K; The AC terminal of the rectifier bridge Q2 is connected in series with a phase-shifting capacitor C5 and then connected to the two ends of the current induction coil H of the main winding. The DC anode of the rectifier bridge Q2 is connected to the low-voltage DC voltage V0. The amplitude adjustment resistors R8 and R9 are connected in series, with one end connected to the DC cathode of the rectifier bridge Q2 and the other end grounded. The collector of the amplitude adjustment transistor BG7 is connected to the DC cathode of the rectifier bridge Q2, and the emitter of the amplitude adjustment transistor BG7 is connected to the DC anode of the rectifier bridge Q2. The base of transistor BG7 is connected in series with bias resistor R6 and timing charging resistor R6, and then connected to the first isolated DC power supply V1. The connection node between bias resistor R5 and bias resistor R6 is connected to the emitter of reverse switching transistor BG4 and the collector of switching transistor BG5. The emitter of switching transistor BG5 is connected to the emitter of reset transistor BG6 and one end of timing charging capacitor C7. The other end of timing charging capacitor C7 is connected to the DC anode of rectifier bridge Q2. Reset transistor BG7... The collector of transistor BG6 is connected to the DC anode of rectifier bridge Q2. The base of reset transistor BG6 is connected to the collector of reverse switching transistor BG4, the base of switching transistor BG5, and one end of reset bias resistor R7. The other end of reset bias resistor R7 is connected to the DC anode of rectifier bridge Q2. The base of reverse switching transistor BG4 is connected to the collector of switching transistor BG3. The emitter of switching transistor BG3 is grounded. The base of switching transistor BG3 is connected to the cathode of reset diode D3. One end of the trigger capacitor C6 is connected to the DC cathode of the rectifier bridge Q2, and the anode of the reset diode D3 is grounded. The emitter of the bias switching transistor BG8 is connected to the first isolated DC power supply V1, and the collector of the bias switching transistor BG8 serves as the carrier amplitude signal output terminal of the secondary winding carrier amplitude circuit. The base of the bias switching transistor BG8 is connected to the anode of the thyristor K, and the cathode of the thyristor K is connected in parallel to the time-delay discharge capacitor C8 and the time-delay discharge resistor R. 10 After grounding, the cathode of the thyristor K is also connected to the thyristor shutdown transistor BG. 10 The collector of the thyristor K is connected to the cathode of the trigger diode D4, and the anode of the trigger diode D4 is connected to the DC cathode of the rectifier bridge Q2; the thyristor turns off transistor BG. 10 The emitter is connected to the first isolated DC power supply V1, and the thyristor shuts down the transistor BG. 10 The base is connected to the current-limiting resistor R. 11 The collector of the current comparison switching transistor BG9 is connected to the collector of the current comparison switching transistor BG9. The emitter of the current comparison switching transistor BG9 is connected to the series junction of the amplitude adjustment resistor R8 and the amplitude adjustment resistor R9. The base of BG9 is connected to pin 6 of the lower transistor IC3 and the lower transistor IC4 in the secondary winding carrier drive circuit. The series junction of the amplitude adjustment resistor R8 and the amplitude adjustment resistor R9 is also connected to the anode of the overload protection diode D5. The cathode of the overload protection diode D5 is grounded.

7. The capacitor phase-shifting motor system circuit according to claim 1, characterized in that, The switching power supply circuit includes transformer E05, capacitor C9, and capacitor C. 10 Capacitor C 11 Capacitor C 12 Capacitor C 13 Resistance R 12 Resistance R 13 Resistance R 14 Zener diode W3, transistor BG 11 Transistor BG 12 Transistor BG 13 Diodes D6, D7, D8, and D9; The transformer E05 includes two primary coils and three secondary coils, namely a first primary coil, a second primary coil, a first secondary coil, a second secondary coil, and a third secondary coil; One end of the first primary coil is connected to the positive terminal of the DC power supply, and the other end of the first primary coil is connected to the transistor BG. 11 The collector of the transistor BG 11 The emitter of the transistor is connected to the isolated ground of the DC power supply, and the transistor BG... 11 Base connection resistor R 12 One end of the resistor is connected to the cathode of the Zener diode W3, and the resistor R is connected to the cathode of the Zener diode W3. 12 The other end is connected to the positive terminal of the DC power supply, and the anode of the Zener diode W3 is connected to the capacitor C. 10 The negative terminal of diode D6 is connected to the anode of diode D6, and the cathode of diode D6 is connected to one end of the second primary coil. The other end of the second primary coil is connected to capacitor C. 10 The positive terminals of all components are connected to the isolated ground wire of the DC power supply; resistor R 13 After being connected in series with capacitor C9, one end is connected to transistor BG. 11 The base of one diode is connected to the cathode of the other diode; The second-stage coil is connected in series with diode D8 and capacitor C. 12 Connect them in parallel, and then use the two ends of the parallel connection as the positive and negative terminals of the second isolated DC power supply V2; The third-stage coil is connected in series with diode D9 and capacitor C. 13 Connect them in parallel, and then use the two ends of the parallel connection as the positive and negative terminals of the third isolated DC power supply V3; The first-stage coil is connected in series with diode D7 and capacitor C. 11 Connected in parallel, the two ends of the parallel connection serve as the positive terminal and ground terminal of the first isolation DC power supply V1; transistor BG 13 The emitter of transistor BG is connected to the ground terminal of the first isolation DC power supply V1. 13 The collector of the transistor BG is connected. 12 The base and resistor R 14 One end, resistor R 14 The other end and transistor BG 12 The collectors of transistors BG are all connected to the positive terminal of the first isolated DC power supply V1. 12 emitter and transistor BG 13 After being connected to the base, it serves as the output terminal of the low-voltage DC voltage V0.

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