Backward irrigation prevention circuit with adjustable turn-on current and energy storage power supply

Abstract

The utility model provides an anti-backflow circuit with adjustable turn-on current and an energy storage power supply. The anti-backflow circuit with the adjustable starting current comprises a current detection circuit and a voltage comparison control circuit. The current detection circuit comprises a current detection operational amplifier and a current detection resistor; the voltage comparison control circuit comprises a voltage comparison operational amplifier and an output control MOS tube, the detection output end of the current detection operational amplifier is connected with the comparison input end of the voltage comparison operational amplifier, and the comparison reference end of the voltage comparison operational amplifier is used for receiving a pulse width adjusting signal; the comparison output end of the voltage comparison operational amplifier is connected with the control end of the output control MOS tube, the first end of the output control MOS tube is connected with the second end of the current detection resistor, and the second end of the output control MOS tube is used for being connected with a power output positive electrode. When an external load and current exist, the duty ratio of the pulse width adjusting signal is adjusted, so that the starting current for outputting and controlling the MOS tube is conveniently adjusted.

Description

Technical Field

[0001] This disclosure relates to the field of energy storage technology, and in particular to an anti-reverse current circuit with adjustable start-up current and an energy storage power supply. Background Technology

[0002] Lithium-ion batteries, with their high energy density, high power density, and long lifespan, have distinguished themselves among chemical energy storage devices. They are already widely used and technologically mature in portable electronics, and their demand is now experiencing explosive growth in electric vehicles and large-scale energy storage. During use, lithium-ion batteries are protected against overcurrent, overvoltage, short circuits, and reverse current flow through their onboard protection boards. Ordinary diodes are among the most commonly used electronic components. Their most significant characteristic is unidirectional conductivity, meaning current can only flow from the anode to the cathode. Utilizing this unidirectional conductivity, ordinary diodes are typically used for rectification and detection. However, due to the presence of a PN junction, ordinary diodes suffer from high losses and generate significant heat when carrying large currents, making them prone to burnout. While MOSFETs generate less heat when carrying large currents, they lack unidirectional conductivity and cannot provide reverse current protection. Therefore, the ideal diode was designed to achieve both high current carrying capacity, unidirectional conductivity, and reverse current protection.

[0003] However, the ideal diodes commonly used in the market can achieve high current flow and unidirectional conduction, but their turn-on voltage and turn-on current are not adjustable. The turn-on current is determined by the internal resistance of the MOSFET. However, under the requirement of high current, it is usually necessary to select a MOSFET with low internal resistance. The low internal resistance of the MOSFET results in a very large turn-on current, such as more than 5A, which makes it impossible to achieve the function of an ideal diode at low current. Utility Model Content

[0004] The purpose of this disclosure is to overcome the shortcomings of the prior art and to provide an anti-reverse current circuit and energy storage power supply that are both adjustable in the start-up current and prevent reverse current leakage.

[0005] The purpose of this disclosure is achieved through the following technical solution:

[0006] An adjustable-current reverse-current protection circuit includes: a current detection circuit and a voltage comparison control circuit; the current detection circuit includes a current detection operational amplifier and a current detection resistor, the first detection terminal of the current detection operational amplifier is connected to the positive terminal of the power input, the first detection terminal of the current detection operational amplifier is also connected to the first terminal of the current detection resistor, and the second detection terminal of the current detection operational amplifier is connected to the second terminal of the current detection resistor; the voltage comparison control circuit includes a voltage comparison operational amplifier and an output control MOSFET, the detection output terminal of the current detection operational amplifier is connected to the comparison input terminal of the voltage comparison operational amplifier, the comparison reference terminal of the voltage comparison operational amplifier is used to receive a pulse width adjustment signal; the comparison output terminal of the voltage comparison operational amplifier is connected to the control terminal of the output control MOSFET, the first terminal of the output control MOSFET is connected to the second terminal of the current detection resistor, and the second terminal of the output control MOSFET is connected to the positive terminal of the power output.

[0007] In one embodiment, the voltage comparison control circuit further includes a voltage comparison switch transistor, the comparison output terminal of the voltage comparison operational amplifier is connected to the control terminal of the voltage comparison switch transistor, the first terminal of the voltage comparison switch transistor is connected to the control terminal of the output control MOS transistor, and the second terminal of the voltage comparison switch transistor is grounded.

[0008] In one embodiment, the voltage comparison switch is an NPN transistor, and the output control MOS transistor is a P-type MOS transistor.

[0009] In one embodiment, the voltage comparison control circuit further includes a first resistor, and the comparison output terminal of the voltage comparison operational amplifier is connected to the control terminal of the voltage comparison switch through the first resistor.

[0010] In one embodiment, the voltage comparison control circuit further includes a second resistor, the first end of which is connected to the control terminal of the voltage comparison switch, and the second end of which is grounded.

[0011] In one embodiment, the voltage comparison control circuit further includes a third resistor, and the first terminal of the voltage comparison switch is connected to the control terminal of the output control MOS transistor through the third resistor.

[0012] In one embodiment, the voltage comparison control circuit further includes a fourth resistor and an output Zener diode. The control terminal of the output control MOS transistor is connected to the first terminal of the fourth resistor and the anode of the output Zener diode, respectively. The second terminal of the output control MOS transistor is connected to the second terminal of the fourth resistor and the cathode of the output Zener diode, respectively.

[0013] In one embodiment, the voltage comparison control circuit further includes a fifth resistor and a first capacitor. The detection output terminal of the current detection operational amplifier is connected to the first terminal of the fifth resistor, the second terminal of the fifth resistor is connected to the comparison input terminal of the voltage comparison operational amplifier, and the second terminal of the fifth resistor is also grounded through the first capacitor.

[0014] In one embodiment, the adjustable-current anti-reverse-current circuit further includes a current adjustment circuit, which includes a sixth resistor, a seventh resistor, an eighth resistor, a second capacitor, and a third capacitor. The first terminal of the sixth resistor is connected to a reference power supply, and the second terminal of the sixth resistor is grounded through the seventh resistor. The second terminal of the sixth resistor is used to receive a pulse width adjustment signal. The second terminal of the sixth resistor is also connected to the first terminal of the eighth resistor and the first terminal of the second capacitor, respectively. The second terminal of the eighth resistor is connected to the first terminal of the third capacitor and the comparison reference terminal of the voltage comparator operational amplifier, respectively. The second terminals of the second capacitor and the second terminals of the third capacitor are both grounded.

[0015] An energy storage power supply includes the anti-reverse current circuit with adjustable start-up current as described in any of the above embodiments.

[0016] Compared with the prior art, this disclosure has at least the following advantages:

[0017] When there is no external load, there is no current in the current sensing resistor, and the current sensing op-amp outputs a low level, which makes the voltage at the comparison input terminal of the voltage comparator op-amp less than the comparison reference voltage, thereby causing the voltage comparator op-amp to output a low level, which in turn turns off the output control MOSFET to prevent external voltage from flowing back to the positive terminal of the power supply input.

[0018] When there is an external load and current, current flows through the current sensing resistor, and the current sensing op-amp outputs a high level. This causes the voltage at the comparator input of the voltage comparator op-amp to be greater than the comparator reference voltage, thus causing the voltage comparator op-amp to output a high level. This, in turn, turns on the output control MOSFET, enabling unidirectional single-pass from the positive input terminal to the positive output terminal of the power supply. Furthermore, by adjusting the duty cycle of the pulse width modulation signal, the comparator reference voltage can be easily adjusted, which in turn facilitates the adjustment of the turn-on voltage of the output control MOSFET, and consequently, the turn-on current of the output control MOSFET. Attached Figure Description

[0019] To more clearly illustrate the technical solutions of the embodiments of this disclosure, the accompanying drawings used in the embodiments will be briefly described below. It should be understood that the following drawings only show some embodiments of this disclosure and should not be regarded as a limitation of the scope. For those skilled in the art, other related drawings can be obtained based on these drawings without creative effort.

[0020] Figure 1 This is a circuit diagram of an adjustable-current anti-reverse-current circuit in one embodiment.

[0021] Figure 2 for Figure 1 The circuit diagram shown is of the current detection circuit in the adjustable-current anti-reverse-current circuit.

[0022] Figure 3 for Figure 1 The circuit diagram shown is of the voltage comparison control circuit in the adjustable current anti-reverse current circuit.

[0023] Figure 4 for Figure 1 The circuit diagram shown is for the current regulation circuit in the anti-reverse current adjustable circuit. Detailed Implementation

[0024] To facilitate understanding of this disclosure, a more complete description will be given below with reference to the accompanying drawings, which illustrate preferred embodiments of the present disclosure. However, this disclosure can be implemented in many different forms and is not limited to the embodiments described herein. Rather, these embodiments are provided to provide a more thorough and complete understanding of the disclosure.

[0025] It should be noted that when an element is referred to as being "fixed to" another element, it can be directly attached to the other element or there may be an intervening element. When an element is referred to as being "connected to" another element, it can be directly connected to the other element or there may be an intervening element. The terms "vertical," "horizontal," "left," "right," and similar expressions used herein are for illustrative purposes only and do not represent the only possible implementation.

[0026] Unless otherwise defined, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this disclosure belongs. The terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of this disclosure. The term "and / or" as used herein includes any and all combinations of one or more of the associated listed items.

[0027] This disclosure relates to an adjustable-current-to-backflow protection circuit. In one embodiment, the adjustable-current-to-backflow protection circuit includes a current detection circuit and a voltage comparison control circuit; the current detection circuit includes a current-sensing operational amplifier and a current-sensing resistor, the first detection terminal of the current-sensing operational amplifier is connected to the positive terminal of the power input, the first detection terminal of the current-sensing operational amplifier is also connected to the first terminal of the current-sensing resistor, and the second detection terminal of the current-sensing operational amplifier is connected to the second terminal of the current-sensing resistor; the voltage comparison control circuit includes a voltage comparison operational amplifier and an output control MOSFET, the detection output terminal of the current-sensing operational amplifier is connected to the comparison input terminal of the voltage comparison operational amplifier, the comparison reference terminal of the voltage comparison operational amplifier is used to receive a pulse width adjustment signal; the comparison output terminal of the voltage comparison operational amplifier is connected to the control terminal of the output control MOSFET, the first terminal of the output control MOSFET is connected to the second terminal of the current-sensing resistor, and the second terminal of the output control MOSFET is connected to the positive terminal of the power output. When there is no external load, there is no current in the current sensing resistor, and the current sensing op-amp outputs a low level. This causes the voltage at the comparator input of the voltage comparator op-amp to be lower than the reference voltage, resulting in the voltage comparator op-amp outputting a low level. This, in turn, turns off the output control MOSFET, preventing external voltage from flowing back into the positive power input. When there is an external load and current, current flows through the current sensing resistor, and the current sensing op-amp outputs a high level. This causes the voltage at the comparator input of the voltage comparator op-amp to be higher than the reference voltage, resulting in the voltage comparator op-amp outputting a high level. This, in turn, turns on the output control MOSFET, enabling unidirectional single-pass from the positive power input to the positive power output. Furthermore, by adjusting the duty cycle of the pulse width modulation signal, the reference voltage can be easily adjusted, which in turn allows for adjustment of the turn-on voltage of the output control MOSFET, and consequently, the turn-on current of the output control MOSFET.

[0028] Please see Figure 1 This is a circuit diagram of an anti-reverse current circuit with adjustable start-up current according to an embodiment of the present disclosure.

[0029] One embodiment of the adjustable-current anti-reverse-current circuit 10 includes a current detection circuit 100 and a voltage comparison and control circuit 200. Please refer to both. Figure 2 The current detection circuit 100 includes a current detection operational amplifier U1 and a current detection resistor RS1. The first detection terminal of the current detection operational amplifier U1 is connected to the positive power input terminal Power_IN+, and the first detection terminal of the current detection operational amplifier U1 is also connected to the first terminal of the current detection resistor RS1. The second detection terminal of the current detection operational amplifier U1 is connected to the second terminal of the current detection resistor RS1. Please refer to [further details omitted]. Figure 3The voltage comparison control circuit 200 includes a voltage comparison operational amplifier U2 and an output control MOSFET M1. The detection output terminal of the current detection operational amplifier U1 is connected to the comparison input terminal of the voltage comparison operational amplifier U2, and the comparison reference terminal of the voltage comparison operational amplifier U2 is used to receive the pulse width adjustment signal MCU-PWM-IN. The comparison output terminal of the voltage comparison operational amplifier U2 is connected to the control terminal of the output control MOSFET M1. The first terminal of the output control MOSFET M1 is connected to the second terminal of the current detection resistor RS1, and the second terminal of the output control MOSFET M1 is used to connect to the positive power output terminal Power_OUT+.

[0030] In this embodiment, when there is no external load, there is no current in the current sensing resistor RS1, and the current sensing operational amplifier U1 outputs a low level, causing the voltage at the comparison input terminal of the voltage comparator operational amplifier U2 to be less than the comparison reference voltage. This causes the voltage comparator operational amplifier U2 to output a low level, which in turn turns off the output control MOSFET M1, preventing external voltage from flowing back into the positive power input terminal Power_IN+. When there is an external load and current, current flows through the current sensing resistor RS1, and the current sensing operational amplifier U1 outputs a high level, causing the voltage at the comparison input terminal of the voltage comparator operational amplifier U2 to be greater than the comparison reference voltage. This causes the voltage comparator operational amplifier U2 to output a high level, which in turn turns on the output control MOSFET M1, achieving unidirectional single-pass from the positive power input terminal Power_IN+ to the positive power output terminal Power_OUT+. Furthermore, by adjusting the duty cycle of the pulse width modulation signal MCU-PWM-IN, the comparison reference voltage can be easily adjusted, which in turn facilitates the adjustment of the turn-on voltage of the output control MOSFET M1, thereby adjusting the turn-on current of the output control MOSFET M1.

[0031] In one embodiment, please refer to Figure 3 The voltage comparison control circuit 200 further includes a voltage comparison switch Q1. The comparison output terminal of the voltage comparison operational amplifier U2 is connected to the control terminal of the voltage comparison switch Q1. The first terminal of the voltage comparison switch Q1 is connected to the control terminal of the output control MOS transistor M1, and the second terminal of the voltage comparison switch Q1 is grounded. In this embodiment, the voltage comparison switch Q1 is located between the comparison output terminal of the voltage comparison operational amplifier U2 and the control terminal of the output control MOS transistor M1. The voltage comparison switch Q1 serves as the output conversion component of the voltage comparison operational amplifier U2, facilitating the adjustment and control of the on / off state of the output control MOS transistor M1. This allows the voltage comparison result of the voltage comparison switch Q1 to be used as a signal for adjusting the on / off state of the output control MOS transistor M1, making the on / off state of the output control MOS transistor M1 easier to control.

[0032] In another embodiment, the voltage comparison switch Q1 is an NPN transistor, with its first terminal being the collector and its second terminal being the emitter, and its control terminal being the base. The output control MOSFET M1 is a P-type MOSFET, with its first terminal being the drain and its second terminal being the source, and its control terminal being the gate. When there is current in the current sensing resistor RS1, the high-level output of the current sensing operational amplifier U1 serves as the comparison input voltage for the voltage comparator operational amplifier U2, causing the output of the voltage comparator operational amplifier U2 to synchronously reach a high level. This means the voltage at the control terminal of the voltage comparator switch Q1 is high, thus turning on the voltage comparator switch Q1. Consequently, the control terminal of the output control MOSFET M1 is grounded, also turning on the output control MOSFET M1. Conversely, when there is no current in the current sensing resistor RS1, the current sensing operational amplifier U1 outputs a low level, causing the voltage comparator operational amplifier U2 to output a low level, thus turning off both the voltage comparator switch Q1 and the output control MOSFET M1.

[0033] In one embodiment, please refer to Figure 3 The voltage comparison control circuit 200 further includes a first resistor R2. The comparison output terminal of the voltage comparison operational amplifier U2 is connected to the control terminal of the voltage comparison switch Q1 through the first resistor R2. In this embodiment, the first resistor R2 is located between the comparison output terminal of the voltage comparison operational amplifier U2 and the control terminal of the voltage comparison switch Q1, that is, the first resistor R2 is connected in series between the comparison output terminal of the voltage comparison operational amplifier U2 and the control terminal of the voltage comparison switch Q1. The first resistor R2 limits the current output by the voltage comparison operational amplifier U2 to avoid current surge to the control terminal of the voltage comparison switch Q1, thus ensuring the normal operation of the voltage comparison switch Q1.

[0034] Furthermore, the voltage comparison control circuit 200 also includes a second resistor R3. The first end of the second resistor R3 is connected to the control terminal of the voltage comparison switch Q1, and the second end of the second resistor R3 is grounded. In this embodiment, the second resistor R3 is connected to both the control terminal and the second terminal of the voltage comparison switch Q1, i.e., the second resistor R3 is connected in parallel to both the control terminal and the second terminal of the voltage comparison switch Q1. The second resistor R3 serves as a fast-turn-on resistor between the control terminal and the second terminal of the voltage comparison switch Q1, enabling rapid conduction of both terminals and improving the static stability of the voltage comparison switch Q1. Moreover, the second resistor R3 and the first resistor R2 form a voltage divider circuit. The voltage across the second resistor R3 serves as the on / off voltage of the voltage comparison switch Q1, facilitating the provision of a stable voltage for the on / off switching of the voltage comparison switch Q1.

[0035] In another embodiment, the voltage comparison control circuit 200 further includes a third resistor R4, and the first terminal of the voltage comparison switch Q1 is connected to the control terminal of the output control MOSFET M1 through the third resistor R4. In this embodiment, the third resistor R4 is connected to both the first terminal of the voltage comparison switch Q1 and the control terminal of the output control MOSFET M1. Specifically, the third resistor R4 is connected in series between the first terminal of the voltage comparison switch Q1 and the control terminal of the output control MOSFET M1, and the third resistor R4 serves as a current-limiting resistor to prevent excessive current from flowing through the control terminal of the output control MOSFET M1.

[0036] In one embodiment, please refer to Figure 3 The voltage comparison control circuit 200 further includes a fourth resistor R5 and an output Zener diode Z1. The control terminal of the output control MOSFET M1 is connected to the first terminal of the fourth resistor R5 and the anode of the output Zener diode Z1, respectively. The second terminal of the output control MOSFET M1 is connected to the second terminal of the fourth resistor R5 and the cathode of the output Zener diode Z1, respectively. In this embodiment, the fourth resistor R5 is connected in parallel to the control terminal and the second terminal of the output control MOSFET M1. The fourth resistor R5 and the third resistor R4 form a voltage divider circuit to provide the on / off voltage for the output control MOSFET M1. The output Zener diode Z1 is also connected in parallel to the control terminal and the second terminal of the output control MOSFET M1. The output Zener diode Z1 serves as the on / off voltage regulator for the output control MOSFET M1, making the on-state voltage of the output control MOSFET M1 more stable and facilitating precise on / off control of the output control MOSFET M1.

[0037] In one embodiment, please refer to Figure 3The voltage comparison control circuit 200 further includes a fifth resistor R11 and a first capacitor C7. The detection output terminal of the current sensing operational amplifier U1 is connected to the first terminal of the fifth resistor R11, and the second terminal of the fifth resistor R11 is connected to the comparison input terminal of the voltage comparison operational amplifier U2. The second terminal of the fifth resistor R11 is also grounded through the first capacitor C7. In this embodiment, the fifth resistor R11 is connected in series between the detection output terminal of the current sensing operational amplifier U1 and the comparison input terminal of the voltage comparison operational amplifier U2. The fifth resistor R11 limits the current of the output signal of the current sensing operational amplifier U1 to prevent the comparison signal current received at the comparison input terminal of the voltage comparison operational amplifier U2 from being too large. The first capacitor C7 is connected in parallel to the comparison input terminal of the voltage comparison operational amplifier U2 to filter the comparison input signal of the voltage comparison operational amplifier U2, thereby improving the acquisition accuracy of the comparison input signal of the voltage comparison operational amplifier U2 and thus improving the accuracy of the output result of the voltage comparison operational amplifier U2.

[0038] In one embodiment, please refer to Figure 4 The adjustable-current anti-reverse-current circuit further includes a current adjustment circuit 300, which includes a sixth resistor R9, a seventh resistor R10, an eighth resistor RZ2, a second capacitor C5, and a third capacitor C6. The first terminal of the sixth resistor R9 is connected to the reference power supply DC_3.3V, and the second terminal of the sixth resistor R9 is grounded through the seventh resistor R10. The second terminal of the sixth resistor R9 is used to receive the pulse width adjustment signal MCU-PWM-IN. The second terminal of the sixth resistor R9 is also connected to the first terminal of the eighth resistor RZ2 and the first terminal of the second capacitor C5. The second terminal of the eighth resistor RZ2 is connected to the first terminal of the third capacitor C6 and the comparison reference terminal of the voltage comparator operational amplifier U2. The second terminals of the second capacitor C5 and the second terminals of the third capacitor C6 are both grounded. In this embodiment, the sixth resistor R9 and the seventh resistor R10 form a bias voltage input circuit to generate a bias voltage, facilitating the application of the pulse width modulation signal MCU-PWM-IN onto the bias voltage. This makes the voltage at the comparison reference terminal of the voltage comparator operational amplifier U2 adjustable, thereby making the comparison reference voltage of the voltage comparator operational amplifier U2 adjustable, and consequently, the turn-on voltage of the output control MOS transistor M1 adjustable. The eighth resistor RZ2, the second capacitor C5, and the third capacitor C6 form a π-type filter to filter the bias voltage onto which the pulse width modulation signal MCU-PWM-IN is applied, making the comparison reference voltage of the voltage comparator operational amplifier U2 more stable.

[0039] In another embodiment, please refer to Figure 4The current regulation circuit 300 further includes a ninth resistor R6, a tenth resistor R7, a fourth capacitor C3, and a fifth capacitor C4. The first terminal of the ninth resistor R6 receives the pulse width modulation signal MCU-PWM-IN. The second terminal of the ninth resistor R6 is connected to the first terminal of the tenth resistor R7, and the second terminal of the ninth resistor R6 is also grounded through the fourth capacitor C3. The second terminal of the tenth resistor R7 is connected to the second terminal of the sixth resistor R9, and the second terminal of the tenth resistor R7 is also grounded through the fifth capacitor C4. In this embodiment, the ninth resistor R6, the tenth resistor R7, the fourth capacitor C3, and the fifth capacitor C4 form a second-order low-pass filter to convert the pulse width modulation signal MCU-PWM-IN into a low-voltage DC signal, which is then superimposed with the bias voltage to adjust the comparison reference voltage of the voltage comparator operational amplifier U2, thereby adjusting the turn-on voltage of the output control MOS transistor M1.

[0040] In one embodiment, this disclosure also relates to an energy storage power supply, including the anti-reverse current adjustable circuit described in any of the above embodiments. In this embodiment, the anti-reverse current adjustable circuit includes a current detection circuit and a voltage comparison control circuit; the current detection circuit includes a current detection operational amplifier and a current detection resistor, the first detection terminal of the current detection operational amplifier is connected to the positive input terminal of the power supply, the first detection terminal of the current detection operational amplifier is also connected to the first terminal of the current detection resistor, and the second detection terminal of the current detection operational amplifier is connected to the second terminal of the current detection resistor; the voltage comparison control circuit includes a voltage comparison operational amplifier and an output control MOSFET, the detection output terminal of the current detection operational amplifier is connected to the comparison input terminal of the voltage comparison operational amplifier, the comparison reference terminal of the voltage comparison operational amplifier is used to receive a pulse width adjustment signal; the comparison output terminal of the voltage comparison operational amplifier is connected to the control terminal of the output control MOSFET, the first terminal of the output control MOSFET is connected to the second terminal of the current detection resistor, and the second terminal of the output control MOSFET is connected to the positive output terminal of the power supply. When there is no external load, there is no current in the current sensing resistor, and the current sensing op-amp outputs a low level. This causes the voltage at the comparator input of the voltage comparator op-amp to be lower than the reference voltage, resulting in the voltage comparator op-amp outputting a low level. This, in turn, turns off the output control MOSFET, preventing external voltage from flowing back into the positive power input. When there is an external load and current, current flows through the current sensing resistor, and the current sensing op-amp outputs a high level. This causes the voltage at the comparator input of the voltage comparator op-amp to be higher than the reference voltage, resulting in the voltage comparator op-amp outputting a high level. This, in turn, turns on the output control MOSFET, enabling unidirectional single-pass from the positive power input to the positive power output. Furthermore, by adjusting the duty cycle of the pulse width modulation signal, the reference voltage can be easily adjusted, which in turn allows for adjustment of the turn-on voltage of the output control MOSFET, and consequently, the turn-on current of the output control MOSFET.

[0041] The embodiments described above are merely illustrative of several implementations of this disclosure, and while the descriptions are specific and detailed, they should not be construed as limiting the scope of this patent disclosure. It should be noted that those skilled in the art can make various modifications and improvements without departing from the concept of this disclosure, and these all fall within the protection scope of this disclosure. Therefore, the protection scope of this patent disclosure should be determined by the appended claims.

Claims

1. A reverse-current protection circuit with adjustable start-up current, characterized in that, include: A current detection circuit includes a current detection operational amplifier and a current detection resistor. The first detection terminal of the current detection operational amplifier is connected to the positive terminal of the power input. The first detection terminal of the current detection operational amplifier is also connected to the first terminal of the current detection resistor. The second detection terminal of the current detection operational amplifier is connected to the second terminal of the current detection resistor. A voltage comparison control circuit includes a voltage comparison operational amplifier and an output control MOSFET. The detection output terminal of the current detection operational amplifier is connected to the comparison input terminal of the voltage comparison operational amplifier. The comparison reference terminal of the voltage comparison operational amplifier is used to receive a pulse width adjustment signal. The comparison output terminal of the voltage comparison operational amplifier is connected to the control terminal of the output control MOSFET. The first terminal of the output control MOSFET is connected to the second terminal of the current detection resistor. The second terminal of the output control MOSFET is used to connect to the positive terminal of the power supply output.

2. The anti-reverse current adjustable circuit according to claim 1, characterized in that, The voltage comparison control circuit further includes a voltage comparison switch transistor. The comparison output terminal of the voltage comparison operational amplifier is connected to the control terminal of the voltage comparison switch transistor. The first terminal of the voltage comparison switch transistor is connected to the control terminal of the output control MOS transistor, and the second terminal of the voltage comparison switch transistor is grounded.

3. The anti-reverse current adjustable circuit according to claim 2, characterized in that, The voltage comparison switch is an NPN transistor, and the output control MOSFET is a P-type MOSFET.

4. The anti-reverse current adjustable circuit according to claim 2, characterized in that, The voltage comparison control circuit further includes a first resistor, and the comparison output terminal of the voltage comparison operational amplifier is connected to the control terminal of the voltage comparison switch through the first resistor.

5. The anti-reverse current adjustable circuit according to claim 2, characterized in that, The voltage comparison control circuit further includes a second resistor, the first end of which is connected to the control terminal of the voltage comparison switch, and the second end of which is grounded.

6. The anti-reverse current adjustable circuit according to claim 2, characterized in that, The voltage comparison control circuit also includes a third resistor, and the first terminal of the voltage comparison switch is connected to the control terminal of the output control MOS transistor through the third resistor.

7. The anti-reverse current adjustable circuit according to claim 1, characterized in that, The voltage comparison control circuit further includes a fourth resistor and an output Zener diode. The control terminal of the output control MOS transistor is connected to the first terminal of the fourth resistor and the anode of the output Zener diode, respectively. The second terminal of the output control MOS transistor is connected to the second terminal of the fourth resistor and the cathode of the output Zener diode, respectively.

8. The anti-reverse current adjustable circuit according to claim 1, characterized in that, The voltage comparison control circuit further includes a fifth resistor and a first capacitor. The detection output terminal of the current detection operational amplifier is connected to the first terminal of the fifth resistor, the second terminal of the fifth resistor is connected to the comparison input terminal of the voltage comparison operational amplifier, and the second terminal of the fifth resistor is also grounded through the first capacitor.

9. The anti-reverse current adjustable circuit according to claim 1, characterized in that, The adjustable-current anti-reverse-current circuit further includes a current adjustment circuit, which includes a sixth resistor, a seventh resistor, an eighth resistor, a second capacitor, and a third capacitor. The first terminal of the sixth resistor is connected to a reference power supply, and the second terminal of the sixth resistor is grounded through the seventh resistor. The second terminal of the sixth resistor is used to receive a pulse width adjustment signal. The second terminal of the sixth resistor is also connected to the first terminal of the eighth resistor and the first terminal of the second capacitor, respectively. The second terminal of the eighth resistor is connected to the first terminal of the third capacitor and the comparison reference terminal of the voltage comparator operational amplifier, respectively. The second terminals of the second capacitor and the second terminals of the third capacitor are both grounded.

10. An energy storage power source, characterized in that, Includes an anti-reverse current circuit with adjustable start-up current as described in any one of claims 1 to 9.

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