NPF type radio frequency device

Abstract

Radio Frequency Device (10) of NPF type comprising a first end terminal E1, four first branches named BR10, BR11, BR12, BR13 connected to E1 and each comprising: a capacitor, respectively C0, C1, C2, C3, of the same capacitance, comprising a first terminal and a second terminal connected to ground, and a switch arranged between E1 and the first terminal of the capacitor of said first branch; said device (10) being adapted to, in each first branch BR1i, close the switch at each instant , during , with natural integer and period of the clock signal;the device comprising at least two successive second branches from an ordered set of second branches BR20, BR21, BR22, BR23, the second branch BR2i comprising a second end terminal E2i, and each second branch of the device BR2k comprising, for each first branch, BR1i, i = 0 to 3, a switch between the first terminal of the capacitor Ci and said second branch, said device being adapted to close said switch at each , during . Figure for the abstract: Fig. 6;

Description

Title of the invention: NPF type radio frequency device Technical field

[0001] The invention lies in the field of differential IQ generator devices (or differential IQ combiners) at radiofrequency (RF) frequencies, i.e. for example 0.1-5GHz or beyond. It is based on the exploitation of a base of so-called N-path filters (in English "N-Path Filters"), hereinafter called NPF and corresponding to N parallel capacitors switched by clock signals with a duty cycle of 1 / N. These architectures naturally offer frequency filtering with a high quality factor.

[0002] As is known and illustrated in Figure 11, left part, an IQ generator receives an input signal, VRF>antet, which makes it possible to obtain at the output two quadrature signals, called I+ and Q+, of the same frequency and phase-shifted by 90°: / + = VRFma çp and Q+ = VRFout (generator 81) or four signals in the case of a differential IQ generator with, in addition, I = - VRF <mit, œ = Vrf,ont,is œ et Q = - Vrf,ont, 90° = rf,mit, 270° (générateur 81').

[0003] By way of reciprocity, the function of such a device can be reversed, by exchanging input(s) and output(s): we then obtain an IQ combiner 82 (possibly differential 82') as illustrated in figure 11 right part. Such an IQ combiner (also called in English "IQ Combiner") receives as inputs two quadrature signals of the same frequency and phase shifted by 90°: / + = VRFitu 0» and Q+ = VRFin 9œ (combiner 82) or four signals in the case of the differential IQ combiner with, in addition, / = -VRF.in.W~ VRFjnMW and Q = ' RFjn, 90° = V RFjn, 270° (combiner 82'), combines them and delivers the signal VRF>out. Prior art

[0004] J. Kaukovuori, K. Stadius, J. Ryynanen, and KAI Halonen, “Analysis and Design of Passive Polyphase Filters,” IEEE Transactions on Circuits and Systems I: Regular Papers, vol. 55, no. 10, pp. 3023-3037, Nov. 2008, doi: 10.1109 / TCSI.2008.917990, proposes, as shown in Figure 1, two polyphase filters, PPF-I and PPF-II, for generating differential quadrature / and Q signals ( / +, I, Q+, Q ). Each of the filters has 4 paths.

[0005] However, these PPF architectures have the following defects: - they do not exhibit, or have little, frequency selectivity of the processed radiofrequency signal, which makes the associated receivers sensitive to blockers in the case where the input signal is the signal received by an RF receiver; - they are not frequency agile; - they are bulky; - they theoretically present at least 3dB of losses between the RF input and the I, Q outputs.

[0006] There is therefore a need to have IQ generators (or IQ combiners), in particular differential ones, at RF frequencies (0.1-5GHz and beyond) and based on N-path filters which do not have these drawbacks. Summary of the invention

[0007] To this end, according to a first aspect, the present invention describes a RadioFrequency device of NPF type comprising a first end terminal, four first branches named BR10, BR11, BR12, BR13 connected to said first end terminal, each first branch comprises a capacitor, respectively Co, Ci, C2, C3, of the same capacitance, comprising a first terminal and a second terminal, said second terminal of the capacitor being connected to ground and a switch arranged between the first end terminal and the first terminal of the capacitor of said first branch; said device being adapted to, in each first branch BR1;, close the switch at each instant pT^ + (j) Tq / 4, during a time interval T() / 4, where P is a natural integer and To the period of the clock signal; said device being characterized in that: the device comprises at least two successive second branches from an ordered set of second branches BR20, BR2b BR22, BR23, the second branch BR2; comprising a second end terminal E2;, and each second branch of the device BR2k comprises, for each first branch, BR1;, i = 0 to 3, a switch between the first terminal of the capacitor C; of said first branch and said second branch, said device being adapted to close said switch at each instant pT0 + (i + k) Tq / 4, during a time interval To / 4.

[0008] The invention thus proposes an NPF type architecture generating (or conversely combining) N amplitude-balanced signals, with a period delayed relative to each other by Tq / N. The architecture reduces losses: approximately 1.8 dB per path (compared to the 3 dB losses per path of the PPF-I and PPF-II filters).

[0009] It requires neither resistance nor inductance, which reduces the size compared to the phase shifters of the prior art.

[0010] In embodiments, such a device will further comprise at least one of the following features: - it comprises four second branches BR20, BR2i, BR22, BR23 each comprising a second end terminal respectively E20, E2b E22 and E23 and each second branch BR2k, k = 0 to 3, comprises, for each first branch, BR1;, i = 0 to 3, a switch between the first terminal of the capacitor Q of said first branch and said second branch, said device being adapted to close said switch at each instant pT^ + ( i: + k ) Tq / 4, during a time interval T0 / 4 - it further comprises a complex filter, the transfer function of which is not symmetrical with respect to zero, and at the input of which the signals delivered to the second end terminals are provided at the input of said complex filter.

[0011] According to another aspect, the invention describes a method for generating IQ signals using said device according to the first aspect of the invention, said method comprising the following steps: - applying an input signal to said first end terminal, - obtaining at least two quadrature signals on the second end terminals of at least said two successive second branches.

[0012] In one embodiment, this generation method using said device according to the first aspect of the invention in the indicated configuration where it comprises four second branches BR20, BR2i, BR22, BR23comprises the following steps: - applying an input signal to said first end terminal, - obtaining the differential signal / +, respectively Q\ Q on the second end terminal E20, respectively E22, E2bE23.

[0013] According to another aspect, the invention provides a method for combining quadrature IQ signals using the device according to the first aspect of the invention, said method comprising the following steps: - application of two quadrature signals, one on the second end terminal of one of the two successive second branches, the other on the second end terminal of the other of the two successive second branches; - obtaining a signal from the combination of said quadrature signals on said first end terminal.

[0014] In one embodiment, this generation method using said device according to the first aspect of the invention in the indicated configuration where it comprises four second branches BR20, BR2b BR22, BR23comprises the following steps: - application of the differential signal / +, respectively g* Q on the second end terminal E20, respectively E22, E2bE23 - obtaining a signal from the combination of said differential signals on said first end terminal. Brief description of the drawings

[0015] The invention will be better understood and other features, details and advantages will become apparent. will appear better on reading the following description, given without limitation, and thanks to the attached figures, given as examples.

[0016] [Fig. 1] [Fig.l] comprises the prior art polyphase filter schemes for generating IQ signals;

[0017] [Fig.2] [Fig.2] is a timing diagram of the electrical signals implemented in an NPF of the type shown in [Fig.3];

[0018] [Fig.3] [Fig.3] is a diagram of an architecture of a classic N-Path Filter - N-Path Mixer;

[0019] [Fig.4] Figure 4 is a timing diagram of the signal V rf^m. in an NPF of the type represented in [Fig.3];

[0020] [Fig.5] [Fig.5] models the circuit of [Fig.8];

[0021] [Fig.6] [Fig.6] represents an NPF device in one embodiment of the invention, adapted to generate and / or combine differential I, Q signals;

[0022] [Fig.7] [Fig.7] is an equivalent diagram of the NPF device of [Fig.6];

[0023] [Fig.8] [Fig.8] is a frequency representation of 4 IQ signals generated in an embodiment of the invention;

[0024] [Fig.9] [Fig.9] is a time representation of differential IQ signals generated in one embodiment of the invention;

[0025] [Fig. 10] [Fig. 10] is a time representation of combined differential IQ signals in one embodiment of the invention;

[0026] [Fig. 11] [Fig. 11] schematically represents an IQ generator, a differential IQ generator, an IQ combiner and a differential IQ combiner;

[0027] [Fig. 12] [Fig. 12] illustrates a case of use of an IQ generator in one embodiment of the invention.

[0028] Identical references may be used in different figures when they designate identical or comparable elements.

[0029] Detailed description: Preamble on N-Path Filters NPF

[0030] As a preamble, some generalities on N-Path Filters NPF are first presented.

[0031] Figures 2, 3, 4 and 5 relate to a classic NPF architecture.

[0032] In these figures, the source signal, for example from an antenna, is named VRFant and its source impedance Ra. The signal VRpjn is the one located after the impedance Ra with respect to the antenna. The equivalent input impedance to the circuit is noted Zin. It will be observed in figures 2 to 5 that Vjjpout — V^p ltl.

[0033] An NPF filter is an electronic circuit which uses N paths, materialized by an identical number N of capacitors in order to improve the rejection of independent signals. sirables. It is often used in RF to reduce the impact of interference due to blockers.

[0034] More specifically, [Fig.3] is a diagram of an architecture of an N-Path Filter -N-Path Mixer.

[0035] Figures 2, 3, 4 illustrate the case N — 4, with the signal VRF^mt ~A(t)cos( wRFt + <p(t) ), A(t) et (p(t) modélisant respectivement la modulation d’amplitude et de phase. Par souci de simplicité, on choisit dans ce qui suit de prendre A(t) — A, constante, et(p(t) = 0° dans les représentations ; les modulations étant des phénomènes lents, cela n’impacte pas la théorie. (ÜRF est la pulsation du signal radiofréquence ; (VRF = 27if où f RF est la fréquence du signal radiofréquence. Le filtre NPF consiste à échantillonner pendant une période To / N, le signal Vrfm sur chacun des chemins de façon à ne charger la capacité correspondante que pendant cet intervalle de temps. L’action est répétée sur chacun des N chemins avec un délai entre les signaux de commande des échantillonneurs (interrupteurs, commutateurs) de TolN. Si œRF est proche de «o ~ f0 ~ / Tq, alors le signal est dans the filter bandwidth where / 0 is the fundamental frequency of the control signal of period To and the corresponding angular frequency. Here, "close" is understood to mean when the distance between the values ​​is less than the half-passband of the filter defined below. Ton is the conduction time of the clock on one phase.

[0036] With reference to figures 2 to 4: the control signal of the sampler intended to supply the capacitor referenced Co is named q>0; the control signal of the sampler intended to supply the capacitor referenced Ci is named q>Q0; the control signal of the sampler intended to supply the capacitor referenced C2 is named <p180 ; le signal de commande de l’échantillonneur destiné à alimenter la capacité référencée C3 est nommé <p27o.

[0037] At the terminals of each capacitor Ci we find a voltage signal, VCb called intermediate frequency FI with pulsation = j œRp - œ0| • For this reason, NPF filters naturally ensuring a mixing function can be used as N-Path Mixer (NPM) in the literature.

[0038] Figure 2 is a timing diagram of the electrical signals (Vrfjn, VRF>ant and the respective control signals q>o,q>9o,q>i8o,q>27o of the switches) implemented in an NPF of the type shown in Figure 3 and Figure 4 is a timing diagram of the signal Vrf,ont, 4>=œ in an NPF circuit of the type shown in Figure 3. It can be clearly seen that VRF.put, ¢)=0° ~ ^RFin

[0039] The equivalent diagram of such a circuit is shown in [Fig.5], differentiating the two functions inherent in the circuit of [Fig.3]: filtering function (corresponding to the FLTR block 110) and mixing function (corresponding substantially to the MX block 120).

[0040] For the mixing function, we find on the VBB node, a pulsation signal œFi modulated in amplitude and in phase by A(t) and <p(t) • Vbb représente indifféremment (c’est-à-dire, quel que soit i) la tension VCi aux bornes de la capacité C,.

[0041] For the filtering function, we are interested in the ratio / , x » RFaril\.f

[0042] The data of the equivalent diagram at the frequency f RF close to the clock frequency of the switches are as follows:

[0043] the dynamic resistance equivalent to the N parallel paths,

[0044] with RB the low frequency load resistance (example: that presented by a measuring amplifier),

[0045] where =

[0046] is the input impedance of the circuit at the RF frequency seen from the antenna

[0047] zin = Rsw + Rb || Rsh ( || means "in parallel")

[0048] where Rxh represents the power losses associated with Ra and Rsw due to the up and down-conversion of signal harmonics

[0049] Rsh = aN{R„ + R^

[0050] where _ 2¾ aN~ lN.yN

[0051] with Rsw the switch resistance and Ra the source resistance (or antenna resistance)

[0052] ç = — Cl • the dynamic capacity equivalent to the N capacities C; in parallel. Whatever the i, C{ - CL so that 2RBCB — R^Cl

[0053] Lb~----L_—, the equivalent dynamic inductance of the filtering function tz . 27rU“! ) \ æ \, the voltage across the capacitor G VCi = A(t)cos[(p(t)+—^ p , (p(t) and A(f) being, as a reminder, the slowly variable modulation functions. (figure 3).

[0055] We then have the following amplitude filtering function which naturally has a high quality factor:

[0056] . / ) f _ | I_iz^! _ i ZgFRm. i RF J ' ~ vRr ] “ Z,„+Ra “ Z^Rm*Ra « r Ri zmt 1 JJI [00571 LJ dvCC •+(Â''RF.) R'Kpt-iïZ(R,;^ j

[0058] A special case is that where R^ is chosen so as to have an adaptation in entrance :

[0059] p _ p _ p 1 «,v( t+p) ( M with L ^L_maich p Ra

[0060] The NPF-based structure will always exhibit its filtering characteristic with a particular value for p _ p _ . «B ^.match Rd.(Ra+RSK)

[0061] The invention

[0062] The invention is situated in the context of N-Path filters. It proposes an NPF type architecture generating 4 signals, sampled, with a period delayed relative to each other by To / 4, balanced in amplitude.

[0063] By way of reciprocity, the invention also makes it possible to respond to the inverse problem, namely to combine 4 periodic signals of period Tü out of phase with each other by To / 4, balanced in amplitude.

[0064] [Fig.6] represents an architecture of a 4-path NPF type device 10 in one embodiment of the invention, which allows the generation and combination of differential IQ signals.

[0065] The NPF device 10 comprises a first end terminal, El, and four first parallel branches, BR10, BR11, BR12, BR13, each connected to EL. The input voltage of the device, VRF,in, is applied to El and therefore to the terminals of each of these four branches.

[0066] Each of these BRI branches; comprises a switch (or commutator) 20 and a capacitor of value CL (identical for the four capacitors), i = 0 to 3: one terminal of this switch 20 is brought to the voltage VRF,in, and the other terminal of the switch is connected to a first terminal of this capacitor. The second terminal of the capacitor is connected to ground.

[0067] The switch 20 connected to the capacitor C,, i = 0 to 3, is controlled by a control signal named<p90x(i) (i.e. q> 0 for i = 0, q>90 for i = 1, q>i80 for i = 2, <p27o pour i = 3 ) qui le fait se fermer à chaqueinstant pT^ + ( / ) T0 / 4 et ce pendant un intervalle de temps Toi 4, où P est un entier naturel variant de 0 à P, l’interrupteur étant ouvert sinon. Px?o est le temps de fonctionnement du dispositif, qui peut atteindre par exemple plusieurs minutes (plus de 2 / 5 / 10 min par exemple) et Fo prend des valeurs variables, par exemple notamment dans une plage de 0,04 à 10 qs.

[0068] The NPF 10 device therefore has 4 paths: in fact, it has four capacities C,-, i= 0 to 3.

[0069] Each capacitor Ci is thus selectively charged by the input signal of the device, Vrf,in, at the instant pT$+ (î)Tq / 4, during a time interval Tol4, using the respective switch 20 arranged upstream of each capacitor and controlled by the control signal <p90x(i).

[0070] The NPF device 10 comprises four second parallel branches, BR2k, k = 0 to 3. The resistance RL represents the load of the circuit put at the output of the device 10.

[0071] The voltage VCi at the terminals of C„ i = 0 to 3, is applied to the terminals successively of each of these four branches BR20, BR2b BR22, BR23 during a time interval 4, at specific times, using respective switches 20 controlled by the control signals cp^x® as described below.

[0072] The voltage, VCi, across the capacitor C, is thus selectively applied to the branch BR2k at each instant pT^ + ( i + k ) Tq / 4, for a time interval To / 4. The corresponding control signals are indicated at the switches in [Fig.6].

[0073] The value of the voltage across Q is read 4 times, during a time interval ^0 / 4, every pT0 + kTa / 4 where k G [ 0, 3 ], starting, for branch BR20, at time pT^ + ( z ) T4.

[0074] The device 10 comprises 4 second end terminals, E20, E2b E22 and E23.

[0075] rf,ont, <b=œ est le signal de tension sur la branche BR20(aux bornesde la résistance RL of this branch, in E20);

[0076] Vrf,ont, ¢.=90° is the voltage signal on branch BR2i (across the resistor RL of this branch, in E2J;

[0077] ^^„^180° is the voltage signal on branch BR22 (across the resistor RL of this branch, in E22);

[0078] RF,<>ut, ¢=270° is the voltage signal on branch BR23 (across the resistor RL of this branch, in E23);

[0079] The phase named Vrf, <p est la version retardée de kTQl4 (retard de phase of 360 0 fc / 4) of the V rf signal,™, i.e. the delayed version of kTol4, and filtered and sampled, of the VRFant signal.

[0080] The timing diagrams of the voltage LRF,out, =360°æ / 4 are shown opposite the point E2k at this voltage in [Fig.6], for k = 0 to 3.

[0081] The signal VRF.aiit,^f is special in that it reproduces the signal V rfp without delay because the switch allowing charges to be transferred from the capacitor to Rr is open at the same time as the switch allowing the capacitor to be charged. However, since the discharge time Rl-Cî - Rl-Cl is very large compared to T0 (for example more than 10 times larger), discharging the capacitor at the same time as charging it has a similar impact to discharging it for an identical duration of T0 / 4 but without it being charged during this instant, which is the case for the other three signals. 4 sampled period signals were thus generated, delayed relative to each other by Fo / 4, naturally balanced in amplitude.

[0082] The invention makes it possible to respond to the following specific problem: the generation of 2 signals phase-shifted by 90° (IQ Generator), as shown in figure 11 in the form of differential signals / +, Q +, Q- where: I+ — VRFoaf ^0<

[0083] I = ^^^¢=180°

[0084] Q+ = V RP^ut, ¢=900

[0085] Q = VRF,out, ¢=2703 •

[0086]

[0087]

[0088] In order to validate the model, to check the equality of the amplitude of the voltage gains for ¢ = 0 (charge and discharge during the same cycle) and ¢ 0 (charge and discharge during a different cycle), as well as the equal distribution of the delays, two cases were studied as a function of the capacity Cj and are illustrated in figures 8 and 9 for which the outputs yRFmit / yj are loaded by a high impedance Rl = 100M2. The values ​​of the parameters are specified in the legend. Figure 8 is a frequency representation of 4 IQ signals generated in one embodiment of the invention, revealing the amplitude balancing and filtering properties: the 4 output phases are well balanced around the filter center frequency. Just as for NPFs, the filtering properties are related to the value of the capacitance Cj — CL. Figure 9 is a time representation of 2 differential IQ signals generated by the invention, showing the balancing of the delays on the timing diagrams: the 4 output phases clearly have a delay of R relative to each other, corresponding to a 90° phase shift. Thus we find the following differential 1 and Q signals: / = V KF,out, ¢=0°

[0089] / =

[0090] Q+ = V 4,=900

[0091] a = RFout, ¢=2701 •

[0092] The equivalent diagram of such a circuit is shown in [Fig.7], differentiating the two filtering (FLTR block 210) and phase shift (DEq block> 220) functions inherent in the circuit of [Fig.6].

[0093] For the phase shift function, we are interested in the ratio / . \ VRF / M, ( f pp ) VrF.om. .which naturally integrates Avj.F^RF) “ jy- = ..........y 1 KFxïnt\J RR / v RF jh \ J rrJ * f'J Fiw yj RR > the filtering properties of the NPF.

[0094] The data of the equivalent diagram are as follows:

[0095] R^y^R^, the equivalent resistance to the N (with N=4) phase-shifted paths in parallel.

[0096] where Rl — Rl + Rw, is the sum of the low frequency load resistance (example: that presented by a measuring amplifier) ​​and the resistance of the inter- breakers located after the capacity.

[0098] 'Z-in is the input impedance of the circuit at the RF frequency seen from the antenna

[0099] Zin = Rsw + RB || Rsh

[0100] where Rsh represents the power losses associated with Ra and Rm due to the up and down conversion of the signal harmonics

[0101] = +

[0102] where _ aN - lN.yN

[0103] with R the switch resistance and Ra the source resistance (or antenna resistance)

[0104] p _ Q , the dynamic capacity equivalent to the N capacities C, in parallel. Whatever i, Q = CL so that 2RBCB = RLCL

[0105] LB=----, the equivalent dynamic inductance of the filtering function (¾) c. [0Ï06] Va = A(t) ) sinc ( $ ). the voltage across the capacitor C, , (p(t) and A(f) being, as a reminder, the slowly variable modulation functions (figure 6).

[0107] We have the following phase shift function V k G [ 1; N = 4 ], at the frequency close to the clock frequency of the switches:

[0108] / x | vR^ul^ | = | | | | M RI / | VRFcm!(i II rRP) II VA>F / mZ( / fijP) I

[0109] apr | Æf) | _ | Zn i _ II I VRpA fRF} I " II “ II

[0110] | vRFFUt,^fRF} I _ rl i zb i e I ^fJjrf) [°in] and ZB = —;—------ ( >RF ) / (RJ|a's )

[0112] „ . . / X . _ I i / ?£ ! i ' | RF^nt(rf) j Rt+R™- | Z^+R^.+R, |

[0113] By way of reciprocity, the architecture as represented in figure 6 makes it possible to respond to the inverse problem: the combination of 2 differential signals in quadrature (figure 11). The corresponding signals are represented in figure 10, in a case where the 4 inputs are supplied by 4 antennas, of impedance Ra — 50 / 2. The output is high impedance Ri = 100fcf?. The inputs are respectively:

[0114] f on the Vœ input

[0115] / on the Vsœ entrance

[0116] Q+ on input V

[0117] Q on the Vrf input,^ 27œ .

[0118] [Fig. 12] illustrates a generation of IQ signals at the RF frequency in an embodiment of the invention and exploitation of the I and Q signals to implement a complex filter 83 (cf. KW Martin, "Complex signal processing is not complex," in IEEE Transactions on Circuits and Systems I: Regular Papers, vol. 51, no. 9, pp. 1823-1836, Sept. 2004, doi: 10.1109 / TCSI.2004.834522). The first block is an IQ signal generator according to the invention, for example the generator 81 or 81' of [Fig. 11]. The output signals can therefore be differential or not. The following block 83 is a complex filter whose transfer function is not symmetric with respect to zero. It can be an N-path filter or a continuous-time filter (without clock). The advantage over a real filter is that it is easier to control the center frequency and bandwidth independently.Additionally, a complex filter may exhibit better signal rejection than a real filter.

[0119] The advantages conferred by an NPF device according to the invention are in particular: - the natural frequency selectivity of the processed radiofrequency signal, inherent in the fact of using an architecture based on switched capacitors; - associated receptors with low sensitivity to blockers; - an architecture intrinsically tunable over a wide frequency band (typically 0.1 GHz-5 GHz), without deteriorating performance over this band; - a more compact architecture; - an architecture limiting losses per path (1.8 dB).

Claims

Claims

1. Radio Frequency Device (10) of NPF type comprising a first end terminal (El), four first branches named BR10, BRI i, BRI2, BRI3 connected to said first end terminal each first branch comprises a capacitor, respectively Co, Ci, C2, C3, of the same capacitance, comprising a first terminal and a second terminal, said second terminal of the capacitor being connected to ground and a switch arranged between the first end terminal (El) and the first terminal of the capacitor of said first branch; said device (10) being adapted to, in each first branch BRI;, close the switch at each instant pT0 + (i)T^ / 4, during a time interval Tol\ where P is a natural integer and the period of the clock signal;said device (10) being characterized in that: - the device comprises at least two successive second branches from an ordered set of second branches BR20, BR2b BR22, BR23, the second branch BR2; comprising a second end terminal E2;, and - each second branch of the device BR2k comprises, for each first branch, BR1;, i = 0 to 3, a switch between the first terminal of the capacitor C; of said first branch and said second branch, said device being adapted to close said switch at each instant pTG + ( i + k ) Tq / 4, during a time interval T^ / 4.;

2. Radio Frequency Device (10) of NPF type according to claim 1, comprising four second branches BR20, BR2b BR22, BR23 each comprising a second end terminal respectively E20, E2b E22 and E23 and each second branch BR2k, k = 0 to 3, comprises, for each first branch, BR1;, i = 0 to 3, a switch between the first terminal of the capacitor Ci of said first branch and said second branch, said device being adapted to close said switch at each instant pT^ + ( i + k ) To / 4, during a time interval 7o / 4

3. Radio Frequency Device (10) of NPF type according to claim 1 or 2, further comprising a complex filter, the transfer function of which is not symmetrical with respect to zero, and at the input of which the signals delivered to the second end terminals are provided at the input of said complex filter.

4. Method for generating IQ signals using the device (10) according to any one of claims 1 to 3, said method comprising the following steps: - applying an input signal to said first end terminal (El), - obtaining at least two quadrature signals on the second end terminals of at least said two successive second branches.

5. A method of generating differential IQ signals using the device (10) according to claim 2 or claim 3 when combined with claim 2, said method comprising the following steps: - applying an input signal to said first end terminal (El), - obtaining the differential signal / +, respectively Q on the second end terminal E20, respectively E22, E2bE23.

6. Method for combining quadrature IQ signals using the device (10) according to claim 1, said method comprising the following steps: - applying two quadrature signals, one to the second end terminal of one of the two successive second branches, the other to the second end terminal of the other of the two successive second branches; - obtaining a signal resulting from the combination of said quadrature signals on said first end terminal (El).

7. Method for combining IQ signals in quadrature using the device (10) according to claim 2, said method comprising the following steps: - applying the differential signal / +, respectively g* Q to the second end terminal E20, respectively E22, E2bE23 - obtaining a signal resulting from the combination of said differential signals on said first end terminal (El).

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