IQ Passive Mixer with Enhanced Conversion Gain

Abstract

Passive IQ Mixer with Improved Conversion Gain This description relates to an IQ mixer (12) comprising a mixing stage (18) including a first mixer (MixI) and a second mixer (MixQ), and a first inductive block (BI) connected to the first mixer (MixI) and including at least one first inductive component, and a second inductive block (BQ) connected to the second mixer (MixQ) and including at least one second inductive component. Figure for the abbreviation: Fig. 4

Description

Title of the invention: IQ passive mixer with improved conversion gain. Technical field

[0001] This description generally relates to passive IQ mixers. Previous technique

[0002] A radio frequency receiver generally includes an IQ mixer for stepping down a radio frequency current to a quadrature baseband current. An IQ mixer is generally made up of transistors. The conversion gain of the IQ mixer is the ratio of the baseband current to the radio frequency current.

[0003] There is a need to have a high conversion gain. Summary of the invention

[0004] One embodiment overcomes all or part of the disadvantages of known passive IQ mixers.

[0005] One embodiment provides for an IQ mixer comprising: - a mixing stage comprising a first mixer and a second mixer; and - a first inductive block connected to the first mixer and comprising at least one first inductive component and a second inductive block connected to the second mixer and comprising at least one second inductive component.

[0006] According to one embodiment, the mixing stage comprises a first inlet, a second inlet, a first outlet, a second outlet, a third outlet, and a fourth outlet. The first mixer is connected to the first inlet, the second inlet, the first outlet, and the second outlet. The second mixer is connected to the first inlet, the second inlet, the third outlet, and the fourth outlet. The first inductive block is connected to the first and second outlets. The second inductive block is connected to the third and fourth outlets.

[0007] According to one embodiment, the first inductive block comprises a first inductor having first and second terminals, the first terminal being connected to the first output, and a second inductor having third and fourth terminals, the third terminal being connected to the second output.

[0008] According to one embodiment, the first inductive block further comprises a first capacitor connected between the second terminal and the fourth terminal.

[0009] According to one embodiment, the first inductive block comprises a third inductor having the fifth and sixth terminals, a second capacitor connected between the first output and the fifth terminal, and a third capacitor connected between the second output and the sixth terminal.

[0010] According to one embodiment, the first inductive block further comprises a fourth capacitor connected between the first output and the second output.

[0011] According to one embodiment, the first inductive block includes a transformer comprising a fourth inductor connected between the first output and the second output and a fifth inductor connected to the fourth inductor.

[0012] According to one embodiment, the first mixer comprises: - a first MOS transistor whose drain is connected to the first output and whose source is connected to the first input; - a second MOS transistor whose drain is connected to the second output and whose source is connected to the first input; - a third MOS transistor whose drain is connected to the first output and whose source is connected to the second input; and - a fourth MOS transistor whose drain is connected to the second output and whose source is connected to the second input.

[0013] According to one embodiment, the second mixer comprises: - a fifth MOS transistor whose drain is connected to the third output and whose source is connected to the first input; - a sixth MOS transistor whose drain is connected to the fourth output and whose source is connected to the first input; - a seventh MOS transistor whose drain is connected to the third output and whose source is connected to the second input; and - an eighth MOS transistor whose drain is connected to the fourth output and whose source is connected to the second input.

[0014] Another embodiment provides for a radio frequency receiver comprising an antenna, a first amplifier connecting the antenna to the mixing stage of an IQ mixer as defined above, a second amplifier connected to the first inductive block of the IQ mixer, and a third amplifier connected to the second inductive block of the IQ mixer. Brief description of the drawings

[0015] These features and advantages, as well as others, will be described in detail in the following description of particular embodiments, given by way of non-limiting example, in relation to the accompanying figures, among which:

[0016] [Fig.1] is a block diagram of a radio frequency receiver comprising an IQ mixer;

[0017] [Fig.2] is a block diagram of part of the receiver of [Fig.1] with the IQ mixer in differential configuration;

[0018] [Fig.3] is a block diagram of an example of a passive IQ mixer of the receiver of [Fig.2];

[0019] [Fig.4] is a block diagram of an embodiment of the IQ mixer of [Fig.1]

[0020] Figure 5 illustrates an amplitude spectrum of a purely resistive load;

[0021] Figure 6 illustrates an amplitude spectrum of the impedance seen by the mixing stage of the IQ mixer of [Fig.4];

[0022] [Fig.7] is a block diagram of an embodiment of the inductive block of the IQ mixer of [Fig.4];

[0023] [Fig.8] illustrates an amplitude spectrum of the impedance seen by the mixing stage of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.7];

[0024] [Fig.9] is a block diagram of the receiver of [Fig.1] with the IQ mixer of [Fig.4] having the inductive blocks of [Fig.7], illustrating the parameters used to perform simulations;

[0025] [Fig. 10] illustrates curves of evolution of the conversion gain of the IQ mixer of [Fig. 4] having the inductive blocks of [Fig. 7] as a function of the inductance of the inductive blocks for three resistance values;

[0026] [Fig.1 1] illustrates, in the upper part, the spectrum of the current supplying the IQ mixer of [Fig.2] and illustrates, in the lower part, the spectrum of the current supplied by the IQ mixer of [Fig.2];

[0027] Figures 12 and 13 illustrate timing diagrams of signals during the operation of the IQ mixer of [Fig.2];

[0028] [Fig. 14] illustrates, in the upper part, the spectrum of the current supplying the IQ mixer of [Fig.4] having the inductive blocks of [Fig.7] and illustrates, in the lower part, the spectrum of the current supplied by the IQ mixer of [Fig.4] having the inductive blocks of [Fig.7];

[0029] Figures 15 and 16 illustrate timing diagrams of signals during the operation of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.7];

[0030] [Fig. 17] illustrates a model of IQ mixer of [Fig. 2] or 5;

[0031] Fig. 18 illustrates timing diagrams of signals during the operation of the IQ mixer of the [Fig.2] or 5;

[0032] [Fig. 19] illustrates timing diagrams of signals during the operation of the IQ mixer of [Fig. 5];

[0033] [Fig.20] is a block diagram of another embodiment of the inductive block of the IQ mixer of [Fig.4];

[0034] [Fig.21] illustrates an amplitude spectrum of the impedance seen by the mixing stage of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.20];

[0035] [Fig.22] is a block diagram of another embodiment of the inductive block of the IQ mixer of [Fig.4];

[0036] [Fig.23] is a block diagram of the receiver of [Fig.1] with the IQ mixer of [Fig.4] having the inductive blocks of [Fig.22], illustrating the parameters used to perform simulations;

[0037] [Fig.24] illustrates an amplitude spectrum of the impedance seen by the mixing stage of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.22];

[0038] [Fig.25] illustrates a curve of evolution of the conversion gain of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.22] as a function of the inductance of the inductive blocks;

[0039] [Fig.26] illustrates the spectrum of the current supplied by the IQ mixer of [Fig.4] having the inductive blocks of [Fig.22];

[0040] [Fig.27] is a block diagram of another embodiment of the inductive block of the IQ mixer of [Fig.4];

[0041] [Fig.28] illustrates an amplitude spectrum of the impedance seen by the mixing stage of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.27];

[0042] [Fig.29] is a block diagram of another embodiment of the inductive block of the IQ mixer of [Fig.4];

[0043] [Fig.30] illustrates an amplitude spectrum of the impedance seen by the mixing stage of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.29];

[0044] [Fig.31] illustrates a curve of evolution of the conversion gain of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.29] as a function of the inductance of the inductive blocks;

[0045] [Fig.32] illustrates the spectrum of the current supplied by the IQ mixer of [Fig.4] having the inductive blocks of [Fig.29];

[0046] Figure 33 is a block diagram of another embodiment of the inductive block of the IQ mixer of the [Fig.4]; and

[0047] [Fig.34] illustrates an amplitude spectrum of the impedance seen by the mixing stage of the IQ mixer of [Fig.4] having the inductive blocks of [Fig.33]. Description of the implementation methods

[0048] The same elements have been designated by the same reference numerals in the different figures. In particular, the structural and / or functional elements common to the Different embodiments may have the same references and may have identical structural, dimensional and material properties.

[0049] For the sake of clarity, only the steps and elements useful for understanding the described embodiments have been represented and are detailed.

[0050] Unless otherwise specified, when referring to two elements connected together, this means directly connected without intermediate elements other than conductors, and when referring to two elements connected (in English "coupled") together, this means that these two elements can be connected or linked through one or more other elements.

[0051] In the following description, when reference is made to absolute position qualifiers, such as the terms "front", "back", "top", "bottom", "left", "right", etc., or relative position qualifiers, such as the terms "above", "below", "superior", "inferior", etc., or to orientation qualifiers, such as the terms "horizontal", "vertical", etc., reference is made, unless otherwise specified, to the orientation of the figures.

[0052] Furthermore, unless otherwise specified, when referring to a voltage at a node, the difference between the potential at said node and a reference potential Gnd, for example ground, is considered to be equal to 0 V.

[0053] Unless otherwise specified, the expressions "approximately", "about", "significantly", and "in the order of" mean to within 10% or 10°, preferably to within 5% or 5°.

[0054] Fig. 1 is a block diagram of a radio frequency receiver 10.

[0055] The radio frequency receiver 10 comprises: - an ANT antenna; - a low-noise amplifier LNA connected, preferably connected, to the ANT antenna and providing an IRF current to an IN node having a VRF voltage; - a mixer IQ 12 receiving the current Irf and comprising a first mixer Mixt supplying a current IBB1 to a node O, having a voltage VBB1, and a second mixer MixQ supplying a current IBBQ to a node OQ having a voltage VBBQ; - a first processing chain 16, comprising a first transimpedance amplifier TI A, receiving the current IBB1, a first low-pass filter LPF, connected to the output of the first transimpedance amplifier TIAb, and a first analog-to-digital converter ADC, connected to the output of the first low-pass filter LPF, and supplying the first digital data I_data; and - a second 16q processing chain comprising a second TIAQ transimpedance amplifier receiving the IBBQ current, a second LPFQ low-pass filter connected to the output of the second TIAQ transimpedance amplifier, and a second analog-to-digital converter ADCq connected to the output of the second low-pass filter LPFq and providing the second digital data Q_data.

[0056] The first mixer Mixt and the second mixer MixQ form a mixing stage 18. The mixing stage 18 receives a periodic oscillating signal LO provided by an oscillator, not shown. The first mixer Mixt receives a first oscillating signal LO:0°, equal to the oscillating signal LO, and a second oscillating signal LO:180°, equal to the oscillating signal LO shifted by 180°. The second mixer MixQ receives a third oscillating signal LO:90°, equal to the oscillating signal LO shifted by 90°, and a fourth oscillating signal LO:270°, equal to the oscillating signal LO shifted by 270°. The mixer IQ converts the radio frequency current IRF into lower frequency currents IBbi and IBbq, which are then processed by the processing chains 16 and 18. By way of example, the oscillating signal LO corresponds to a square wave with a duty cycle of 50%.Subsequently, the oscillating signals LO:0°, LO:90°, LO: 180° and LO:270° are generally also called SL0 control signals. .

[0057] The [Fig.2] is a block diagram of part of the receiver of the [Fig.1] with the IQ 12 mixer in differential configuration.

[0058] In other words, the IQ 12 mixer has a symmetrical structure. This means that the currents Irf, IBbi, and IBBq and the voltage Vrf are transmitted via symmetrical lines. A symmetrical line is a pair of conductive traces having exactly the same ground relationship, carrying an electrical signal from a source to a load. The voltage Vrf corresponds to the voltage between the two conductive traces of a symmetrical line SL between the low-noise amplifier LNA and the IQ 12 mixer. The current I^ is the current flowing in one of the conductive traces of the symmetrical line SL, the other conductive trace of the symmetrical line SL carrying the current -1^.The voltage VBbi corresponds to the voltage between the two conductive tracks of a balanced line SL! between the mixer IQ 12 and the transimpedance amplifier TIAb, and the voltage VBbq corresponds to the voltage between the two conductive tracks of a balanced line SLQ between the mixer IQ 12 and the transimpedance amplifier TIAQ. The current IBBi is the current flowing in one of the conductive tracks of the balanced line SLb, the other conductive track of the balanced line SL! carrying the current -IBB1, and the current IBBq is the current flowing in one of the conductive tracks of the balanced line SLq, the other conductive track of the balanced line SLQ carrying the current -IBBQ.

[0059] The mixing stage 18 of the IQ 12 mixer comprises: - a first input node II connected to the first conductive track of the balanced line SL connecting the IQ 12 mixer to the low noise amplifier LNA; - a second input node 12 connected to the second conductive track of the balanced line SL connecting the mixer IQ 12 to the low noise amplifier LNA; - a first output node 01! connected to the first conductive track of the balanced line SL! connecting the mixer IQ 12 to the transimpedance amplifier TIA i; - a second output node 02j connected to the second conductive track of the symmetrical line SLi connecting the IQ 12 mixer to the TIA i transimpedance amplifier; - a third output node 01Q connected to the first conductive track of the balanced SLQ line connecting the IQ 12 mixer to the TIA Q transimpedance amplifier; and - a fourth output node 02Q connected to the second conductive track of the balanced SLQ line connecting the IQ 12 mixer to the TIA transimpedance amplifier Q-

[0060] The first mixer Mixt is connected between inputs II and 12 and outputs O1j and O2i. The second mixer MixQ is connected between inputs II and 12 and outputs O1Q and O2q. Hereafter, the mixer IQ 12 of [Fig. 2], which comprises only the mixing stage 18, is referred to as the resistive mixer.

[0061] The voltage Vrf corresponds to the voltage between nodes II and I2. The current Irf is the current arriving at node II. From node II, a current IiNi flows to the mixer Mix! and a current I^q flows to the mixer MixQ. The voltage VBbi corresponds to the voltage between nodes Oh and O2b, and the voltage VBbq corresponds to the voltage between nodes O1Q and O2Q. The current IBBi is the current flowing through node Oh, and the current IBBq is the current flowing through node O1Q.

[0062] Fig. 3 is a block diagram similar to Fig. 2 illustrating an example of an implementation of the passive IQ mixer. In Fig. 3, the IQ 12 mixer is implemented with metal-oxide-semiconductor field-effect transistors, also known as MOS transistors.

[0063] The first Mixi mixer comprises: - a first MOS transistor Th, for example with an N-channel, whose drain is connected, preferably connected, to node Oh, whose source is connected, preferably connected, to node II, and whose gate receives the oscillating signal LO:0; - a second MOS transistor T2b for example with an N channel, whose drain is connected, preferably connected, to node O2b whose source is connected, preferably connected, to node II, and whose gate receives the oscillating signal LO: 180; - a third MOS transistor, for example N-channel, whose drain is connected, preferably connected, to node 10b, whose source is connected, preferably connected, to node 12, and whose gate receives the oscillating signal LO: 180; and - a fourth MOS transistor T4b for example with an N channel, whose drain is connected, preferably connected, to node O2b, whose source is connected, preferably connected, to node 12, and whose gate receives the oscillating signal LO:0.

[0064] The second MixQ mixer comprises: - a fifth MOS transistor T1Q, for example N-channel, whose drain is connected, preferably connected, to node O1Q, whose source is connected, preferably connected, to node II, and whose gate receives the oscillating signal LO:90; - a sixth MOS transistor T2Q, for example N-channel, whose drain is connected, preferably connected, to node O2Q, whose source is connected, preferably connected, to node II, and whose gate receives the oscillating signal LO:270; - a seventh MOS transistor T3Q, for example an N-channel transistor, whose drain is connected, preferably connected, to node O1Q, whose source is connected, preferably connected, to node 12, and whose gate receives the oscillating signal LO:270; and - an eighth MOS transistor T4Q, for example N-channel, whose drain is connected, preferably connected, to node O2Q, whose source is connected, preferably connected, to node 12, and whose gate receives the oscillating signal LO:90.

[0065] According to one embodiment, the MOS transistors Tlb T2b T3b T4b T1Q, T2Q, T3q and T4q are identical.

[0066] The [Fig.4] is a block diagram of an embodiment of the IQ 12 mixer of the [Fig.1].

[0067] The IQ 12 mixer illustrated in [Fig. 4] comprises the mixing stage 18 of the IQ 12 mixer illustrated in [Fig. 2] and further comprises a first inductive block B! and a second inductive block Bq. The first inductive block B! is located between the first mixer Mixt of the mixing stage 18 and the first transimpedance amplifier TIAb, and the second inductive block Bq is located between the second mixer MixQ of the mixing stage 18 and the second transimpedance amplifier TIAQ.

[0068] According to one embodiment, the first inductive block B! corresponds to a first two-port network and the second inductive block Bq corresponds to a second two-port network. The first two-port network B! has a first input B11, preferably connected to the output O1 of the first mixer Mixb; a second input B12, preferably connected to the output O2 of the first mixer Mixb; a first output BO1; and a second output BO2b. The second two-port network BQ has a first input BI1Q connected, preferably connected, to the output O1Q of the second mixer MixQ; and a second input BI2Q connected, preferably connected, to the output O2Q of the second mixer. MixQ, a first output BOIq and a second output B02Q. The first output BC) 1, and the second output B02! of the first inductive block B! are connected, preferably connected, to the first transimpedance amplifier TIAb. The first output BOIq and the second output B02Q of the second inductive block Bq are connected, preferably connected, to the second transimpedance amplifier TIAQ.

[0069] The first two-port network B! and the second two-port network BQ each include an inductive component, preferably at least one inductor. In one embodiment, the inductance of the first two-port network B! is equal to the inductance of the second two-port network Bq and is called LBB. In the following, the mixer IQ 12 of [Fig. 4] is referred to as the inductive mixer.

[0070] Let ZLNA be the impedance seen by the mixer IQ 12 from inputs II and 12, ZBB1 the impedance seen by the mixing stage 18 from outputs O1 and O2, and ZBBQ the impedance seen by the mixing stage 18 from outputs O1Q and O2Q. The current IBBI(t) is the through impedance of current ZBB1, and the current IBBQ(t) is the through impedance of current ZBBQ. For the sake of simplicity, the impedances ZBB1 and ZBBQ are assumed to be identical and equal to an impedance ZBB.

[0071] Figure 5 is an amplitude spectrum of the impedance ZBB when it is purely resistive. The amplitude of the impedance ZBB is constant and equal to IZBB(0)l.

[0072] Figure 6 is an amplitude spectrum of the ZBB impedance of the IQ 12 mixer shown in Figure 4. The amplitude spectrum includes: - a substantially flat part Fl at least for angular frequencies between -com and com; - a generally decreasing part Deacl at least for angular frequencies between -2coLO and -œm, such that the magnitude IZBB(-2coLO)l of the impedance ZBB at the angular frequency of -2coLO is at least ten times greater than the magnitude IZBB(com)l of the impedance ZBB at the angular frequency of com; and - a globally increasing part Incl for angular frequencies between com and 2coLO, so that the magnitude IZBB(2coLO)l of the impedance ZBB at the angular frequency of 2coLO is at least ten times greater than the magnitude IZBB(com)l of the impedance ZBB at the angular frequency of com.

[0073] The inventor has shown that the conversion gain CG of the inductive mixer is greater than the conversion gain of the resistive mixer.

[0074] Figure 7 is a block diagram of an embodiment of the inductive block B of the mixer IQ of Figure 4. The inductive block BQ may have the same structure as the inductive block Bb.

[0075] The inductive block B! includes a first inductor L1 having a first terminal connected, preferably connected, to the first input Ih and a second terminal connected, preferably connected, to the first output Olb. The inductive block B! includes a second inductor L2 having a first terminal connected, preferably connected, to the second input I2L and a second terminal connected, preferably connected, to the second output O2b. According to one embodiment, the first inductor L1 and the second inductor L2 have the same inductance equal to LBB / 2.

[0076] [Fig.8] illustrates an amplitude spectrum of the impedance ZBB seen by the mixing stage 18 of the mixer IQ 12 of [Fig.4] with the inductive blocks B! and BQ each having the structure illustrated in [Fig.7].

[0077] The amplitude spectrum includes: - a decreasing part Deacl for angular frequencies below -œm, so that the modulus IZBB(-2coLO)l of the impedance ZBB at the angular frequency of -2coLO is at least ten times greater than the modulus IZBB(com)l of the impedance ZBB at the angular frequency of com; - a substantially flat region Fl at least for angular frequencies between -com and com; and - an increasing part Incl for angular frequencies above com, so that the magnitude IZBB(2coLO)l of the impedance ZBB at the angular frequency of 2coLO is at least ten times greater than the magnitude IZBB(com)l of the impedance ZBB at the angular frequency of com.

[0078] Simulations were carried out with the IQ 12 mixer having the structure illustrated in [Fig. 4] with the inductive blocks B! and BQ each having the structure illustrated in [Fig. 7]. For the simulations, the angular frequency coLO is equal to 2*ji*5*109 rad / s and the angular frequency com is equal to 2*ji*106 rad / s.

[0079] Figure 9 is a block diagram of the receiver of Figure 1 with the mixer IQ of Figure 4 having the inductive blocks B1 and BQ of Figure 7, illustrating the parameters used to perform simulations. In Figure 9, each inductor L1 and L2 has an inductance equal to LBB / 2.

[0080] The low-noise amplifier LNA is simulated by an SC current source, providing an RF current Irf at the angular frequency coLO+com, and an impedance ZLNA connected in parallel between inputs II and 12 of the mixer IQ 12. Each transimpedance amplifier TI A, and TIAQ is simulated by an RBB resistor. For the simulations, the mixing stage 18 is considered to have a duty cycle of 50%. The switching resistance of the mixer is zero ohms.

[0081] The conversion gain CG of the mixer IQ 12 is calculated by taking the ratio of the harmonic power of the current IBB1 (assumed equal to IBBQ) at the angular frequency com to the harmonic power of the current Irf at the angular frequency coLO + com.

[0082] Figure 10 illustrates the CGI, CG2, and CG3 curves of the conversion gain CG of the IQ 12 mixer in Figure 4, with the inductive blocks B1 and BQ each having the structure shown in Figure 7, with respect to the inductance LBB for three values ​​of resistance RBB. The CGI curve is obtained with RBB equal to 10 ohms, the CG2 curve is obtained with RBB equal to 100 ohms, and the CG3 curve is obtained with RBB equal to 1 kiloohm. For low values ​​of the inductance LBB, the conversion gain CG is approximately equal to the conversion gain CG obtained for the resistive mixer 12 in Figure 2, i.e., without the inductive blocks B1 and BQ, and tends towards the value 1 / jt, i.e., 0.318. For high values ​​of the inductance LBB, the conversion gain CG tends towards ^2 / n ' c, i.e. 0.798, regardless of the resistance value RBB. The conversion gain CG of the inductive mixer 12 with mixers Mt and MQ having the structure illustrated in [Fig.7] is therefore advantageously superior to the conversion gain of the resistive mixer.

[0083] Fig. 11 illustrates, in the upper part, the spectrum of the current 1^ supplying the resistive mixer of Fig. 2 and illustrates, in the lower part, the spectrum of the current IBB1 supplied by the resistive mixer of Fig. 2.

[0084] For the resistive mixer, the spectrum of the current 1^ has a single peak Prf at the frequency of 5.001 GHz, which corresponds to the angular frequency of coLO+com. For the resistive mixer, the spectrum of the current IBB1 has a peak Pm at the frequency of 1 MHz, which corresponds to the angular frequency of com, with an amplitude equal to 1 / jt, and has peaks P'H2, P'œ, P'œ , P'3, P'h4, and PH4 respectively at the frequencies of 9.999 GHz, 10.001 GHz, 19.999 GHz, 20.001 GHz, 29.999 GHz, 30.001 GHz, which respectively correspond to the angular frequencies of 2coLO-com, 2coLO+com, 3cüLo-tt>m, 3cüLo+tt>m, 4coLO-com, and 4coLO+com, each having a non-zero amplitude.

[0085] Fig. 12 illustrates, for the resistive mixer of Fig. 2, timing diagrams of the currents I1N1 and I1NQ supplying the resistive mixer, of the voltage VRF between nodes II and 12 and of the currents IBB1 and IBBQ supplying the resistive mixer.

[0086] Figure 13 illustrates timing diagrams, on a smaller time scale than Figure 12, of the currents Irf, I1N1 and IBB1 and of the control signal SLo for the resistive mixer of Figure 2. As can be seen in this figure, the current I1N1 is approximately equal to half the current Irf.

[0087] Figure 14 illustrates, in the upper part, the spectrum of the current 1^ supplying the mixer IQ of Figure 4 with the inductive blocks B1 and BQ, each having the structure illustrated in [Fig.7] and illustrates, in the lower part, the spectrum of the current IBB1 supplied by the mixer IQ of [Fig.4] with the inductive blocks B! and Bq each having the structure illustrated in [Fig.7].

[0088] For the inductive mixer, the spectrum of the current I1N1 has a peak P'rfhi at the frequency of 4.999 GHz, which corresponds to the angular frequency of co-coLOm, a peak PRFHi at the frequency of 5.001 GHz, which corresponds to the angular frequency of co+coLOm, a peak P'rfh2 at the frequency of 14.999 GHz, which corresponds to the angular frequency of 2co-co LOm, a peak Prfh2 at the frequency of 15.001 GHz, which corresponds to the angular frequency of 2co+coLOm. For the inductive mixer, the spectrum of the current IBB1 has a peak Pm at the frequency of 1 MHz, which corresponds to the angular frequency of com, with an amplitude equal to y and has peaks P'H2, PH2, P'œ, Pus, respectively at the frequencies of 9.999 GHz, 10.001 GHz, 19.999 GHz, 20.001 GHz, which correspond respectively to the angular frequencies of 2co-coLOm, 2co+coLOm, 3co-(DLOm, 3co+(DLOm), each having an amplitude substantially equal to zero.

[0089] Figure 15 illustrates, for the inductive mixer of Figure 4 with inductive blocks B1 and Bq each having the structure shown in Figure 7, timing diagrams of the currents I1N1 and I1NQ supplying the inductive mixer, the voltage VRF between nodes II and I2, and the currents IBB1 and IBBQ supplied by the inductive mixer. As can be seen in this figure, the currents IBB1 and IBBQ each have a sinusoidal shape.

[0090] Figure 16 illustrates timing diagrams, on a smaller time scale than Figure 15, of the currents Irf, I1N1 and IBB1 and of the control signal SLo for the inductive mixer. As illustrated in this figure, the current I1N1 is not equal to half the current IRF.

[0091] The lowered current spectrum for the inductive mixer has negligible power in all harmonics other than the useful signal at the angular frequency of com or, in other words, all the power of the input radio frequency mixer is lowered to the power of one harmonic at the angular frequency of com.

[0092] Fig. 17 illustrates a Mix mixer model, which corresponds to the Mix! mixer or the MixQ mixer of the IQ 12 mixer, used to explain the increase in the conversion gain of the inductive mixer compared to the conversion gain of the resistive mixer, and Fig. 18 illustrates signal timing diagrams during the operation of the Mix mixer.

[0093] The model includes a current source CS, supplying the current I1N, which corresponds to the current I1N1 or the current I1NQ, to a node 13, the current source CS having a first terminal connected to node 13 and a second terminal connected to the low-potential reference source Gnd, for example ground. The voltage at Node 13 is called V1N. The Mix mixer is modeled by a first switch SW1 controlled by a control signal SLo+ and by a second switch SW2 controlled by a control signal SL0. The first switch SW1 has its first terminal connected to node 13. The second switch SW2 has its first terminal connected to node 13. The inductive block B1 or BQ and the transimpedance amplifier TI A or TIAq are modeled by a first impedance ZBB / 2 with its first terminal connected to a second terminal of the first switch SW1 and a second terminal connected to the low-potential reference source Gnd, and a second impedance ZBB / 2 with its first terminal connected to a second terminal of the second switch SW2 and a second terminal connected to the low-potential reference source Gnd. Each impedance ZBB / 2 carries a current IBB, which corresponds to the current IBB1 or the current IBBQ.The voltage VBB, which corresponds to the voltage VBB1 or the voltage VBBQ, is the voltage across the two impedances ZBB / 2.

[0094] The control signals SLo+ and SLo are square waves, each having a . The period is T. The control signal SLo is offset by 180° relative to the control signal SL0+. The control signal SL0+ corresponds to the oscillating signal LO:0 or the oscillating signal LO:90 described previously when the Mix mixer models the Mixt mixer, and the control signal SL0 corresponds to the oscillating signal LO:180 or the oscillating signal LO:270 described previously when the Mix mixer models the MixQ mixer. Each control signal, SLo+ and SLo, alternates between the value 1 and the value 0. For example, when the control signal SLo+ (respectively SL0) is equal to 1, switch SW1 (respectively SW2) is closed, and when the control signal SL0+ (respectively SL0) is equal to 0, switch SW1 (respectively SW2) is open. The duty cycle of the control signals SLo+ and SL0 is equal to r / T. When the duty cycle is equal to 0.5, this means that T is equal to 2r.The current I1N is phase-shifted by q> with respect to the control signal SL0+, which corresponds to a time shift of qn / jt when T is equal to 2r. For the Mixb mixer, the phase shift q> is equal to 0 and, for the MixQ mixer, the phase shift q> is equal to -ji / 2. In the following description, unless otherwise specified, the control signal SLo refers to either the control signal SLo+ or the control signal Slo•.

[0095] Suppose that the current I1N(t) received by the mixer Mix at node 13 is defined by the following equation:

[0096] [Math.l] UN ( t ) = IMRFcos [ ( œj o+œm ) t ]

[0097] where IMRF is the maximum intensity of the current I1N(t), where coLO is the angular frequency of the oscillating signal SLo, equal to 2ir / T, and where com is the angular frequency of the useful signal.

[0098] In the frequency domain, the current Iin(co) received by the mixer Mix at node 13 is defined by the following equation:

[0099] [Math.2] UN ( œ ) [ ô ( œ ( œLO+œm ) ) d()+ô ( w+ ( ) ) J

[0100] The control signal SL0(t) is equal to the convolution of a rectangular signal and a Dirac comb. In the frequency domain, the control signal SL0(a>) is defined by the following equation:

[0101] [Math.3] SLO ( œ ) =5 sinc( 7 7½ ) EX [ ô ( wn^o ) ]

[0102] The current Ibb(I) supplied by the mixer Mix is ​​equal to the product of the current (t) and the control signal SLo(t). This means that, in the frequency domain, the current IBB(tt>) is equal to the convolution of the current Iin( <o) et du signal de commande SLO(co) et est défini par l'équation suivante :

[0103] [Math.4] Ww) =^TLLsinc(T ) [ô(œ+(nr)coLOœm)&Wô(

[0104] If we only consider the terms for n equal to -1 and 1 and if we consider that com is much less than coLO, the previous equation becomes the following equation:

[0105] [Math.5] I BB ( œ ) [ e-^ô ( ) +6^0 ( œ+œ m ) ] +"^ [ e-it'ô ( œ2œ LO w m ) +0^'6 ( co+2œ LO +œ m ) ]

[0106] which corresponds in the time domain to the following equation:

[0107] [Math.6] IBB (1 ) cos ( wmt+ <p ) +^F cos ( ( 2œLO+æni ) t+tp )

[0108] The conversion gain CG is given by the following equation:

[0109] [Math.7] abs(IBH(to.„)) 1 C'J“abs(I1N(œLO+üJ1„)) ~;T

[0110] This value corresponds to the conversion gain CG obtained by simulation for a resistive mixer.

[0111] Another approach is to use the Math 6 equation for the current IBB(t) in order to determine the conversion gain CG in a different way.

[0112] The voltage VBB(t) is equal to the convolution of the current IbbCO and the impedance ZBB (t). Therefore, in the frequency domain, the voltage VBB(co) is given by the following equation:

[0113] [Math.8] V BB ( w )=^l^sinc(^ ) [^6(^+^1)0^^)2^( (ni) +6^0(^+^+1)10^0+(010)253((11+1)0^0+10 ) j

[0114] The voltage V^t) is equal to the product of the voltage VBB(t) and the control signal SLo(t). Therefore, in the frequency domain, the voltage ViN(co) is equal to the convolution of the voltage VBB(co) and the control signal Slo(w)-

[0115] If we consider that com is much less than coLO, the voltage V^CcoLo+Wm) is given by the following relation:

[0116] [Math.9] V|N(œf o+œ )=3 [sinc2(4F )ZBB((n+l)wLO) 1+53^48^2()ZBB((nl)wLO) ] v \ n^Ol n*0,l +2sinc2 ( y ) ZBB ( œm ) )

[0117] and the voltage V^CcoLo-Wm) is given by the following relation:

[0118] [Math.10] V1N( wLOœ ) (E^- [sinc2(f )zbb((n+1 kb) 1 +£"7 [sinc2(f )ZBB((n 1 )œLO) ] X mz yn*0,1 nX).l +2sinc2 (2) ZBB (oem)) GiU'"

[0119] When the ZBB impedance is purely resistive, equations Math 9 and Math 10 can be simplified to the following equation:

[0120] [Math. 11] VlN ( ^LO~ ) =Z [ ( ) + ( 4 )+^

[0121] If we only consider the terms for n equal to -1, the equation Math 11 becomes the following equations:

[0122] [Math. 12] Vin ( ^LO"^m ) ( wm ) ImrF^ VIN (œLOwm) (Wm) IMRpe-W

[0123] The input radio frequency impedance of the mixer Zj^cüLo+cOm) at coLO+com, with a baseband load of the mixer equal to ZBB(co), is calculated as follows:

[0124] [Math. 13] ZrfI )= 7 ( üu=< [sinc2( Ç )ZBB( (n+l)c^0) ]+E"=»- [sinc2(Ç)ZBB((n 1)«l0) ]+2smc2( 7 )ZBB( wm) ) ' \ nwlj n*t)J /

[0125] The real part RRF(coLo+com) of the impedance at coLO+com of the IQ mixer The input radio frequency with a resistive load is defined by the following equation:

[0126] [Math. 14] R RF( œ LO +œ m ) = I ( [0-5^ ] + [ 0.5^ ]+2^

[0127] The efficiency of the input RF mixer IQ Eff is defined by the following equation:

[0128] [Math. 15] " " " PouÜQ@wm Eli— p —----2Z---- / ~ (in Umrf) KRFRBHœLo+wm)

[0129] The efficiency Eff is equal to 1 when the power to com supplied by the IQ 12 mixer is equal to the input RF power.

[0130] For the resistive mixer, equation Math 15 becomes the following equation:

[0131] [Math. 16]

[0132] The real part Rrp of the radio frequency input of the IQ mixer of the impedance ZRF to coLO+com for the inductive mixer, i.e. with an inductive load ZBB(co) equal to Rbb+JwLbb, in the limiting condition where the impedance IZBB(n(DLo)l at the angular frequency of ncoLO is much greater than the magnitude of the impedance IZBB(Wm)l for all n, n being an integer greater than 1, is calculated as:

[0133] [Math. 17] Rrf ( ) -sine ( f ) Z BB ( œ m ) -é R BB

[0134] For the inductive mixer, the efficiency of the input radio frequency mixer IQ Eff is defined by the following equation:

[0135] [Math. 18] Eff= TICGlbb) OmrfFRbb ​​7(CGlbb)~ (EFrRRdœLO+W„j

[0136] An Eff efficiency equal to 1 corresponds to a conversion gain CG equal to ^2 / ti is the value given by the simulations.

[0137] When the impedance ZBB(tt>) is purely resistive, the current I1N1(t) is equal to Irf(t) / 2. When the impedance ZBb(w) includes an inductive component LBb, the current I1N1(t) includes a component IH1(t) that comes directly from the current IrXO and a component IL1(t) that comes from the mixer MixQ, and the current I1NQ(t) includes a component IHQ(t) that comes directly from the current IRF(t) and a component ILQ(t) that comes from the mixer Mixb

[0138] The current IH^t) is given by the following equation:

[0139] [Math. 19] IHI(t)=cos[(œLO+wm)t]

[0140] In the frequency domain, the current IH^co) is given by the following equation:

[0141] [Math.20] IH^œ)=4 [ $ ( w ( w Lo +w m ))+5( œ+ ( œ LO +œ m) ) ]

[0142] The current IL^t) is given by the following equation:

[0143] [Math.21] IL^Asign ( cos [ ( œLOœm ) t ] ) Beos [ ( œLOœm ) t ]

[0144] where A and B are constants, and where sign(x) is equal to 1 when x is greater than or equal to 0 and sign(x) is equal to -1 when x is less than 0.

[0145] In the frequency domain, the current IL^co) is given by the following equation:

[0146] [Math.22] HE { (œ)=^ sine ( f ) | [ Ô ( œ ( œ LO w m ) ) +Ô ( œ+( œ LO o m ) ) ]

[0147] The relationship between the current IiNi(t) and the currents IH^t) and IL^t) is given by the following equation:

[0148] [Math.23] (tMHjCO+IL^t)

[0149] There is an optimal choice for constants A and B which maximizes the ratio ImdOm ) / IBB(2ncoLO ± com) with an upper limit for constant A fixed by the efficiency condition Eff equal to 1.

[0150] With this choice for the constants A and B, the current IBB^t) is well represented by the following equation:

[0151] [Math.24] lBB(t)~SLo(0 (IHj(t)+ILj(t))=cos[œmt]

[0152] Figure 19 illustrates timing diagrams of signals during the operation of the IQ mixer of Figure 5. The figure shows that the current I1N1(t) is substantially equal to a square wave.

[0153] Figure 20 is a block diagram of another embodiment of the inductive block B of the IQ 12 mixer of Figure 4. The inductive block BQ may have the same structure as the inductive block Bb.

[0154] The inductive block B! illustrated in [Fig. 20] comprises all the elements of the inductive block B! illustrated in [Fig. 7] and further comprises a capacitor Cl, one terminal of which is connected, preferably connected, to the first input Blh and the other terminal of which is connected, preferably connected, to the second input BI2b

[0155] [Fig.21] illustrates an amplitude spectrum of the impedance ZBB seen by the mixing stage 18 of the mixer IQ 12 of [Fig.4] with the inductive blocks B! and BQ each having the structure illustrated in [Fig.20].

[0156] The amplitude spectrum includes: - an increasing part Inc2 for angular frequencies below -2coLO; - a decreasing part Deacl for angular frequencies between -2coLO and -œm, so that the modulus IZBB(-2œL0)l of the impedance ZBb at the angular frequency of -2coLO is at least ten times greater than the modulus IZBB(tt>m)l of the impedance ZBB at the angular frequency of com; - a substantially flat part Fl at least for angular frequencies between -com and com; - an increasing part Incl for angular frequencies between com and 2coLO, such that the magnitude IZBb(2cülo)I of the impedance ZBB at the angular frequency of 2coLO is at least ten times greater than the magnitude IZBB(tt>m)l of the impedance at the angular frequency of com; and - a decreasing part Deac2 for angular frequencies greater than 2coLO.

[0157] Figure 22 is a block diagram of another embodiment of the inductive block B of the IQ 12 mixer of Figure 4. The inductive block Bq may have the same structure as the inductive block Bb.

[0158] The inductive block B! illustrated in [Fig. 22] comprises all the elements of the inductive block B! illustrated in [Fig. 20] and further comprises a capacitor C2 having a first terminal connected, preferably connected, to the first output BO1! and a second terminal connected, preferably connected, to the second output BO2b

[0159] Simulations were carried out with the IQ mixer having the structure illustrated in [Fig. 4] with the inductive blocks B! and BQ each having the structure illustrated in [Fig. 22]. For the simulations, for each inductive block B! and Bq, the capacitor C1 has a capacitance of 70 fF, the capacitor C2 has a capacitance of 7 pF, the inductor L1 has an inductance LBB / 2 of 2 nH, and the inductor L1 has an inductance LBB / 2 of 2 nH.

[0160] The [Fig.23] is a block diagram of the receiver of the [Fig.1] with the mixer IQ of the [Fig.4] and the inductive blocks B! and BQ each having the structure illustrated in the [Fig.22], illustrating the parameters used for the simulations.

[0161] The low-noise amplifier LNA is simulated by a current source SC, an inductor L3, a capacitor C3, and a resistor RI connected in parallel between inputs II and 12 of the mixer IQ. For the simulations, the inductor L3 has an inductance of 2 nH, the capacitor C3 has a capacitance of 500 fF, and the resistor RI has a resistance of 1 kΩ. Each transimpedance amplifier TI A, and TIAQ is simulated by an ideal transconductance differential operational amplifier OTA and a capacitor C4 and a resistor R2 connected in parallel between the inputs and outputs of the ideal transconductance differential operational amplifier OTA. For the simulations, the cutoff frequency of the transimpedance amplifier TI A, and TIAQ is 40 MHz, the capacitor C4 has a capacitance of 250 fF, and the resistor R2 has a resistance of 16 kΩ. For the simulations, the mixing stage 18 is considered with a duty cycle of 50% and an on-state resistance of 50 Ω. In addition, a coupling capacitor C5 is provided for each mixer Mixt and MixQ at each input II and 12. For the simulations, the capacitance of capacitor C5 is 70 fF.

[0162] [Fig.24] illustrates an amplitude spectrum of the impedance ZBB seen by the mixing stage 18 of the mixer IQ of [Fig.4] with the inductive blocks B! and BQ each having the structure illustrated in [Fig.22].

[0163] Figure 25 illustrates a curve showing the evolution of the conversion gain CG of the mixer IQ of Figure 4, with the inductive blocks B1 and BQ each having the structure illustrated in Figure 22, as a function of the inductance LBB of the inductive blocks B1 and BQ. When the inductance LBB becomes high, the conversion gain of the inductive mixer 12 with the mixers M1 and MQ having the structure illustrated in Figure 22 is advantageously greater than the conversion gain of the resistive mixer.

[0164] Figure 26 illustrates the spectrum of currents IBB1 and IBBQ supplied by the IQ mixer of Figure 4 with inductive blocks B1 and Bq each having the structure illustrated in Figure 22 and with inductance LBB equal to 4 nH. The spectrum of current IBB1 has a single peak PH1 at a frequency of 1 MHz, which corresponds to the angular frequency of communication, with an amplitude approximately equal to 0.777. The spectrum of current IBBQ also has a single peak PH1 at a frequency of 1 MHz, which corresponds to the angular frequency of communication, with an amplitude approximately equal to 0.777.

[0165] Figure 27 is a block diagram of another embodiment of the inductive block B of the IQ 18 mixer of Figure 4. The inductive block BQ may have the same structure as the inductive block Bb.

[0166] In the inductive block B! illustrated in [Fig. 27], the first input B1h is connected to the first output BO1, and the second input B12 is connected to the second output BO2b. The inductive block B! further includes a capacitor C6 having a first terminal connected, preferably connected, to the first input B1 and a second terminal connected, preferably connected, to the second input B1. The inductive block B! further includes, connected in series between the first input B1h and the second input B1, a capacitor C7, an inductor L4, and a capacitor C8. The capacitor C7 has a first terminal connected, preferably connected, to the first input B1h and a second terminal connected, preferably connected, to a first terminal of the inductor L4. The capacitor C8 has a first terminal connected, preferably connected, to the second input B12, and a second terminal connected, preferably connected, to a second terminal of the inductor L4.

[0167] Figure 28 illustrates an amplitude spectrum of the impedance ZBB seen by the mixing stage 18 of the mixer IQ 12 of Figure 4, with the inductive blocks B1 and Bq each having the structure illustrated in Figure 27. The amplitude spectrum illustrated in Figure 28 is identical to the amplitude spectrum illustrated in Figure 21.

[0168] Figure 29 is a block diagram of another embodiment of the inductive block B of the IQ 12 mixer of Figure 4. The inductive block Bq may have the same structure as the inductive block Bb.

[0169] The inductive block B! illustrated in [Fig. 29] is identical to the inductive block B! illustrated in [Fig. 27], except for capacitor C6, which is not present. The inductive block B! illustrated in [Fig. 29] therefore comprises, connected in series between the first input BI^ and the second input BI1q, capacitor C7, inductor L4, and capacitor C8.

[0170] Simulations were performed with the IQ mixer having the structure illustrated in [Fig. 4] with the inductive blocks B! and BQ each having the structure illustrated in [Fig. 29]. For the simulations, for each inductive block B! and BQ, capacitor C7 has a capacitance of 2 pF, capacitor C8 has a capacitance of 2 pF, and inductor L4 has an inductance LBB of 3.67 nH. For the simulations, the parameters disclosed previously in relation to [Fig. 23] are also used.

[0171] [Fig.30] illustrates an amplitude spectrum of the impedance ZBB seen by the mixing stage 18 of the mixer IQ of [Fig.4] with the inductive blocks B! and Bq each having the structure illustrated in [Fig.29].

[0172] Figure 31 illustrates a curve showing the evolution of the conversion gain CG of the mixer IQ of Figure 4, with the inductive blocks B1 and BQ each having the structure illustrated in Figure 22, with respect to the inductance LBB of the inductive blocks B1 and BQ. The maximum conversion gain CG is approximately equal to 0.536. When the inductance LBB becomes high, the conversion gain of the inductive mixer 12 with the mixers M1 and MQ having the structure illustrated in Figure 27 is advantageously greater than the conversion gain of the resistive mixer.

[0173] Figure 32 illustrates the spectrum of currents IBB1 and IBBQ supplied by mixer IQ of Figure 4 with inductive blocks B1 and BQ each having the structure illustrated in Figure 29 and with inductance LBB equal to 2 nH. The spectrum of current IBB1 has a peak PH1 at a frequency of 1 MHz, which corresponds to the angular frequency of com, with an amplitude approximately equal to 0.454. The spectrum of current IBBQ also has a single peak PH1 at a frequency of 1 MHz, which corresponds to the angular frequency of com, with an amplitude approximately equal to 0.454.

[0174] Figure 33 is a block diagram of another embodiment of the inductive block B of the IQ 12 mixer of Figure 4. The inductive block Bq may have the same structure as the inductive block Bb.

[0175] The inductive block B! illustrated in [Fig. 33] comprises a transformer T including a primary inductor L5 having a first terminal connected, preferably connected, to the first input BI^ and a second terminal connected, preferably connected, to the second input B12, and a secondary inductor L6 having a first terminal connected, preferably connected, to the first output BO1 and a second terminal connected, preferably connected, to the second output BO2b

[0176] [Fig.34] illustrates an amplitude spectrum of the impedance ZBBi or ZBBQ seen by the mixing stage of the mixer IQ 12 of [Fig.4] with the inductive blocks B! and BQ each having the structure illustrated in [Fig.32].

[0177] The amplitude spectrum includes: - a substantially flat part F2 for angular frequencies below -2coLO; - a decreasing part Deacl for angular frequencies between -2coLO and -œm, so that the modulus IZBB(-2œL0)l of the impedance ZBB at the angular frequency of -2coLO is at least ten times greater than the modulus IZBB(com)l of the impedance ZBB at the angular frequency of com; - a substantially flat part Fl at least for angular frequencies between -com and com; - an increasing portion Incl for angular frequencies between com and 2coLO, such that the magnitude IZBB(2coLO)l of the impedance ZBB at the angular frequency of 2coLO is at least ten times greater than the magnitude IZBB(com)l of the impedance ZBB at the angular frequency of com; and - a substantially flat part F3 for angular frequencies above 2coLO.

[0178] Various embodiments and variations have been described. A person skilled in the art will understand that certain features of these various embodiments and variations could be combined, and other variations will become apparent to a person skilled in the art.

[0179] Finally, the practical implementation of the embodiments and variants described is within the reach of a person skilled in the art, based on the functional indications given above.

Claims

Demands

1. Mixer IQ (12) comprising: - a mixing stage (18) comprising a first mixer (MixO and a second mixer (MixQ); and - a first inductive block (B,) connected to the first mixer (MixO) and comprising at least one first inductive component (L1, L2; L4; L5, L6) and a second inductive block (BQ) connected to the second mixer (MixQ) and comprising at least one second inductive component (L1, L2; L4; L5, L6).

2. IQ mixer according to claim 1, wherein the mixing stage (18) comprises a first inlet (II), a second inlet (12), a first outlet (O10), a second outlet (O20), a third outlet (O1Q) and a fourth outlet (O2Q), wherein the first mixer (MixJ) is connected to the first inlet (II), the second inlet (12), the first outlet (O10) and the second outlet (O20), wherein the second mixer (MixQ) is connected to the first inlet (II), the second inlet (12), the third outlet (O1Q) and the fourth outlet (O2Q), wherein the first inductive block (BO) is connected to the first outlet (O10) and the second outlet (O20), and wherein the second inductive block (Bq) is connected to the third outlet (O1Q) and the fourth outlet (O2Q).

3. IQ mixer according to claim 2, wherein the first inductive block (BO) comprises a first inductor (L1) having first and second terminals, the first terminal being connected to the first output (Oh), and a second inductor (L2) having third and fourth terminals, the third terminal being connected to the second output (020).

4. IQ mixer according to claim 3, wherein the first inductive block (BO) further comprises a first capacitor (C2) connected between the second terminal and the fourth terminal.

5. IQ mixer according to claim 2, wherein the first inductive block (BO) comprises a third inductor (L4) having fifth and sixth terminals, a second capacitor (C7) connected between the first output (O10) and the fifth terminal, and a third capacitor (C8) connected between the second output (O20) and the sixth terminal.

6. IQ mixer according to claim 3 or 5, wherein the first inductive block (B^ further comprises a fourth capacitor (Cl; C6) connected between the first output (01) and the second output (02^).

7. IQ mixer according to claim 2, wherein the first inductive block (BJ) comprises a transformer (T) comprising a fourth inductor (L5) connected between the first output (Oh) and the second output (O2^ and a fifth inductor (L6) connected to the fourth inductor (L5).

8. Mixer IQ according to any one of claims 1 to 7, wherein the first mixer (MixO) comprises: - a first MOS transistor (Th) whose drain is connected to the first output (Oh) and whose source is connected to the first input (II); - a second MOS transistor (T2^) whose drain is connected to the second output (O2J) and whose source is connected to the first input (II); - a third MOS transistor (T3i) whose drain is connected to the first output (Oh) and whose source is connected to the second input (12); and - a fourth MOS transistor (T40) whose drain is connected to the second output (O2J) and whose source is connected to the second input (12).

9. Mixer IQ according to claim 8, wherein the second mixer (MixQ) comprises: - a fifth MOS transistor (T1Q) whose drain is connected to the third output (01Q) and whose source is connected to the first input (II); - a sixth MOS transistor (T2q) whose drain is connected to the fourth output (02Q) and whose source is connected to the first input (II); - a seventh MOS transistor (T3q) whose drain is connected to the third output (01Q) and whose source is connected to the second input (12); and - an eighth MOS transistor (T4Q) whose drain is connected to the fourth output (02Q) and whose source is connected to the second input (12).

10. Radio frequency receiver (10) comprising an antenna (ANT), a first amplifier (LNA) connecting the antenna (ANT) to the mixing stage (18) of an IQ mixer (12) according to any one of claims 1 to 9, a second amplifier (TIAO) connected to the first inductive block (BO) of the IQ mixer (12), and a third amplifier (TIAQ) connected to the second inductive block (BQ) of the IQ mixer (12).

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