Rotating electrical machine control device and program

Abstract

To provide a rotating electrical machine control device and a program with which it is possible to simplify a system.SOLUTION: A rotating electrical machine is configured such that a voltage is induced to the field winding of a rotor causing a field current to flow when a high frequency voltage is applied to a stator winding. A control device 30 performs switching control of an inverter so that a composite voltage of a high frequency voltage and a fundamental wave voltage of lower frequency than the high frequency voltage is applied to the stator winding, and adjusts the exciting voltage component of the field winding, which is a voltage component included in the composite voltage, so that the output voltage of the inverter is lowered to a limit value or below.SELECTED DRAWING: Figure 5

Description

[Technical field]

[0001] The present disclosure relates to a control device and a program for a rotating electric machine. [Background technology]

[0002] Conventionally, a system is known that includes a rotating electric machine having a stator including a stator winding, and a first power converter electrically connected to the stator winding. The rotating electric machine has a rotor including a field winding. The system further includes a second power converter for passing a field current through the field winding. Such a system is described in, for example, Patent Document 1. [Prior art documents] [Patent documents]

[0003] [Patent Document 1] Japanese Patent Application Publication No. 5-30774 Summary of the Invention [Problem to be solved by the invention]

[0004] The above system requires a second power converter in addition to the first power converter, making the system configuration complicated. Also, in the above system, the field current is reduced by the second power converter after the voltage of the first power converter reaches a limit value, so it takes a long time for the voltage to be reduced after reaching the limit value.

[0005] A primary object of the present disclosure is to provide a control device and program for a rotating electric machine that can simplify the system. [Means for solving the problem]

[0006] The present disclosure provides a rotating electric machine having a stator including a stator winding and a rotor including a field winding, an inverter electrically connected to the stator winding; A control device for a rotating electric machine applied to a system including: The rotating electric machine is configured such that a high-frequency voltage is applied to the stator winding to induce a voltage in the field winding, causing a field current to flow, a switch control unit that performs switching control of the inverter so as to apply a composite voltage of the high-frequency voltage and a fundamental voltage having a frequency lower than that of the high-frequency voltage to the stator winding; an adjustment unit that performs an adjustment process to adjust a voltage component included in the composite voltage, the excitation voltage component of the field winding, so that the output voltage of the inverter is equal to or lower than a limit value; Equipped with.

[0007] The rotating electric machine of the present disclosure is configured such that a high-frequency voltage is applied to the stator winding to induce a voltage in the field winding, causing a field current to flow. Also, the switching control of the inverter is performed by the switch control unit so that a high-frequency voltage having a higher frequency than the fundamental voltage is passed to the stator winding in addition to a fundamental voltage intended to generate torque in the rotating electric machine. This eliminates the need for a power converter other than the inverter for passing a field current through the field winding, simplifying the system.

[0008] In the present disclosure, a process is performed to adjust the excitation voltage component of the field winding, which is a voltage component included in the applied voltage of the stator winding, so that the output voltage of the inverter is equal to or lower than a limit value. This makes it possible to prevent the magnetic flux of the rotor from becoming too large and to expand the operating range of the high-speed side of the rotating electric machine. In addition, since the excitation voltage component included in the applied voltage of the stator winding is adjusted, the output voltage of the inverter can be quickly reduced. [Brief description of the drawings]

[0009] [Figure 1] 1 is an overall configuration diagram of a control system for a rotating electric machine according to a first embodiment; [Diagram 2] FIG. 2 is a diagram showing an inverter and its peripheral configuration. [Diagram 3] FIG. [Figure 4] FIG. 4 is a diagram showing an electric circuit provided in the rotor. [Diagram 5] FIG. 4 is a block diagram of a torque control process of the control device. [Figure 6] 1 is a diagram showing a fundamental wave current and a high frequency current (harmonic current). [Figure 7] FIG. 2 is a diagram showing an operating region of a rotating electric machine. [Figure 8] FIG. 4 is a block diagram showing a calculation process of a d-axis high-frequency command current of the control device. [Figure 9] 5 is a flowchart showing the procedure of a calculation process of a d-axis high-frequency command current. [Figure 10] FIG. 11 is a block diagram of a torque control process according to a second embodiment. [Figure 11] FIG. 4 is a diagram showing map information defining the amplitude and fluctuation frequency of a d-axis high-frequency command current. [Figure 12] 5 is a flowchart showing the procedure of a calculation process of a d-axis high-frequency command current. [Figure 13] FIG. 13 is a block diagram showing a calculation process of a d-axis high-frequency command current according to the third embodiment. [Figure 14] FIG. 13 is a block diagram of a torque control process according to a fourth embodiment. [Figure 15] FIG. 4 is a block diagram showing a calculation process of an inductance decreasing current. [Figure 16] 10 is a flowchart showing a procedure for a process of calculating an inductance decreasing current. [Figure 17] 13 is a flowchart showing the procedure of a torque control process according to a fifth embodiment. [Figure 18] FIG. 13 is a block diagram of a gain adjustment process according to the sixth embodiment. [Figure 19] FIG. 4 is a graph showing the relationship between the amplitude and gain of a d-axis high-frequency current. [Figure 20] FIG. 23 is a block diagram of a gain adjustment process according to the seventh embodiment. [Figure 21] FIG. 4 is a diagram showing the relationship between the amplitude and gain of a fundamental wave current. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

[0010] Several embodiments will be described with reference to the drawings. In several embodiments, functionally and / or structurally corresponding and / or associated parts may be given the same reference numerals or reference numerals with different digits of 100 or more. For corresponding and / or associated parts, the description of other embodiments may be referred to.

[0011] First Embodiment A first embodiment of a rotating electric machine and a control device for the rotating electric machine according to the present disclosure will be described below with reference to the drawings. The rotating electric machine and the control device configure a control system for the rotating electric machine, and the control system is mounted on a vehicle. The rotating electric machine is a power source for driving the vehicle.

[0012] 1, the control system includes a DC power supply 10, an inverter 20, a control device 30, and a rotating electric machine 40. The rotating electric machine 40 is a self-excited field winding type synchronous machine. For example, a mechanically and electrically integrated drive device may be configured by including the rotating electric machine 40, the inverter 20, and the control device 30, or the rotating electric machine 40, the inverter 20, and the control device 30 may each be configured by a respective component.

[0013] The rotating electric machine 40 includes a housing 41, and a stator 50 and a rotor 60 housed in the housing 41. The rotating electric machine 40 of this embodiment is an inner rotor type rotating electric machine in which the rotor 60 is disposed radially inside the stator 50.

[0014] The stator 50 includes a stator core 51 and a stator winding 52. The stator winding 52 is made of, for example, a copper wire, and includes U-, V-, and W-phase windings 52U, 52V, and 52W that are arranged offset from each other by 120° in electrical angle.

[0015] The rotor 60 includes a rotor core 61 and a field winding 70. The field winding 70 is made of, for example, aluminum wire, copper wire, or CNT (carbon nanotube). A rotating shaft 32 is inserted through a central hole of the rotor core 61. The rotating shaft 32 is rotatably supported by the housing 41 via a bearing 42.

[0016] As shown in FIG. 2, the inverter 20 includes a series connection of U-, V-, and W-phase upper-arm switches SUp, SVp, and SWp and U-, V-, and W-phase lower-arm switches SUn, SVn, and SWn. First ends of the U-, V-, and W-phase windings 52U, 52V, and 52W are connected to the connection points of the U-, V-, and W-phase upper-arm switches SUp, SVp, and SWp and the U-, V-, and W-phase lower-arm switches SUn, SVn, and SWn. Second ends of the U-, V-, and W-phase windings 52U, 52V, and 52W are connected at the neutral point. That is, in this embodiment, the U-, V-, and W-phase windings 52U, 52V, and 52W are star-connected. In this embodiment, each of the switches SUp to SWn is an IGBT. A freewheel diode is connected in inverse parallel to each of the switches SUp to SWn.

[0017] The collectors of the U-, V-, and W-phase upper-arm switches SUp, SVp, and SWp are connected to a positive terminal of a DC power supply 10. The emitters of the U-, V-, and W-phase lower-arm switches SUn, SVn, and SWn are connected to a negative terminal of the DC power supply 10. A smoothing capacitor 11 is connected in parallel to the DC power supply 10.

[0018] Next, the stator 50 and the rotor 60 will be described with reference to FIG.

[0019] The stator 50 and the rotor 60 are both arranged coaxially (specifically, on the central axis O of rotation) with the rotating shaft 32. In the following description, the direction in which the rotating shaft 32 extends is referred to as the axial direction, the direction extending radially from the center of the rotating shaft 32 is referred to as the radial direction, and the direction extending circumferentially around the rotating shaft 32 is referred to as the circumferential direction.

[0020] The stator 50 is made of laminated steel plates made of soft magnetic material, and has an annular back yoke 51a and a plurality of teeth 51b protruding radially inward from the back yoke 51a. A plurality of slots 54 are formed between adjacent teeth 51b and aligned in the circumferential direction. The stator winding 52 is formed by accommodating the phase windings of each phase in each slot 54 in a predetermined order.

[0021] The rotor 60 is made of a soft magnetic material, for example, laminated steel plates. The rotor 60 has a cylindrical rotor core 61 and a plurality of main poles 62 protruding radially outward from the rotor core 61. In this embodiment, eight main poles 62 are provided at equal intervals in the circumferential direction.

[0022] The field winding 70 includes a first winding portion 71a and a second winding portion 71b. In each main pole portion 62, the first winding portion 71a is wound radially outward, and the second winding portion 71b is wound radially inward from the first winding portion 71a. In each main pole portion 62, the winding directions of the first winding portion 71a and the second winding portion 71b are the same. In addition, among the main pole portions 62 adjacent in the circumferential direction, the winding directions of the winding portions 71a and 71b wound around one of the main pole portions 62 are opposite to the winding directions of the winding portions 71a and 71b wound around the other of the main pole portions 62 adjacent in the circumferential direction. Therefore, the magnetization directions of the main pole portions 62 adjacent in the circumferential direction are opposite to each other.

[0023] Fig. 4 shows an electric circuit on the rotor 60 side including the winding portions 71a, 71b wound around a common main pole portion 62. The first winding portion 71a shown in Fig. 4 is a series connection of the first winding portions 71a wound around each main pole portion 62, and the second winding portion 71b shown in Fig. 4 is a series connection of the second winding portions 71b wound around each main pole portion 62.

[0024] The rotor 60 is provided with a diode 80 as a rectifying element and a capacitor 81. The diode 80 is electrically connected in parallel to the series connection of the first winding portion 71a and the second winding portion 71b. In detail, the cathode of the diode 80 is connected to a first end of the first winding portion 71a, and the second end of the first winding portion 71a is connected to a first end of the second winding portion 71b. The anode of the diode 80 is connected to a second end of the second winding portion 71b. The capacitor 81 is electrically connected in parallel to the second winding portion 71b. In FIG. 4, L1 indicates the inductance of the first winding portion 71a, L2 indicates the inductance of the second winding portion 71b, and C indicates the capacitance of the capacitor 81.

[0025] In this embodiment, a series resonant circuit is configured including the first winding portion 71a and the capacitor 81, and a parallel resonant circuit is configured including the second winding portion 71b and the capacitor 81. In Fig. 4, f1 indicates a first resonant frequency which is the resonant frequency of the series resonant circuit, and f2 indicates a second resonant frequency which is the resonant frequency of the parallel resonant circuit.

[0026] Alternatively, the anode of the diode 80 may be connected to the first end of the first winding portion 71a, and the cathode of the diode 80 may be connected to the second end of the second winding portion 71b.

[0027] Returning to the explanation of FIG. 2, the control system includes a current sensor 21, an angle sensor 22, and a voltage sensor 23. The current sensor 21 detects at least two phases of currents flowing through the rotating electric machine 40. The angle sensor 22 detects the rotation angle (electrical angle) of the rotor 60. In this embodiment, the voltage sensor 23 includes a sensor that detects the voltage of the DC power supply 10, and a sensor that detects the output voltage (phase voltage) of each phase of the inverter 20. The detection values ​​of the sensors 21 to 23 are input to the control device 30.

[0028] The control device 30 is an electronic control unit mainly composed of a microcomputer 31. The microcomputer 31 includes a CPU (Central Processing Unit). The functions provided by the microcomputer 31 can be provided by software recorded in a substantial memory device and a computer that executes the software, by software alone, by hardware alone, or by a combination of these. For example, when the microcomputer 31 is provided by an electronic circuit that is hardware, it can be provided by a digital circuit including a large number of logic circuits, or by an analog circuit. For example, the microcomputer 31 executes a program stored in a non-transitory tangible storage medium as a storage unit provided in the microcomputer 31. The program includes, for example, programs for processing shown in Figs. 5, 7, 8, etc., which will be described later. A method corresponding to the program is executed by executing a set of instructions that constitute the program. The storage unit is, for example, a non-volatile memory. The program stored in the storage unit can be updated via a communication network such as the Internet, for example, OTA (Over The Air), etc.

[0029] The control device 30 generates drive signals to turn on and off each of the switches SUp to SWn that constitute the inverter 20. In particular, the control device 30 generates drive signals to turn on and off each of the arm switches SUp to SWn and supplies the generated drive signals to the gates of each of the arm switches SUp to SWn in order to convert the DC power output from the DC power source 10 into AC power and supply it to the U-, V-, and W-phase windings 52U, 52V, and 52W. As a result, in each phase, the upper arm switches and the lower arm switches are alternately turned on with dead times therebetween.

[0030] The control device 30 turns on and off the switches SUp to SWn so as to pass a composite current of a fundamental current and a harmonic current (specifically, a harmonic excitation current) having a higher frequency than the fundamental current through each of the phase windings 52U, 52V, 52W. The fundamental current is a current that mainly serves to generate torque in the rotating electric machine 40. The harmonic current is a current that mainly serves to excite the field winding 70 and induce a field current in the field winding 70. The phase currents flowing through the phase windings 52U, 52V, 52W are shifted by 120° in electrical angle.

[0031] The torque control of the rotating electrical machine 40 executed by the control device 30 will be described with reference to FIG.

[0032] The two-phase conversion unit 100 converts the U-, V-, and W-phase currents in a three-phase fixed coordinate system into a d-axis current Idr and a q-axis current Iqr in a two-phase rotating coordinate system (dq coordinate system) based on the detection value of the current sensor 21 and the electrical angle θe detected by the angle sensor 22.

[0033] The command current calculation unit 101 calculates a d-axis base command current Idbref and a q-axis command current Iqref based on the command torque Tref. The d-axis base command current Idbref and the q-axis command current Iqref are command values ​​of DC components corresponding to a fundamental wave current. The command current calculation unit 101 may calculate the d-axis base command current Idbref and the q-axis command current Iqref based on, for example, map information in which the command torque Tref, the d-axis base command current Idbref, and the q-axis command current Iqref are associated with each other, and the input command torque Tref.

[0034] The excitation current calculation unit 102 calculates the d-axis high frequency command current Idhref. The d-axis high frequency command current Idhref is a command value of an AC component corresponding to a harmonic current that excites the field winding 70, and is expressed by the following equation (eq1) in this embodiment. In the following equation (eq1), Idamp is the amplitude of the d-axis high frequency command current Idhref, and fh is the fluctuating frequency of the d-axis high frequency command current Idhref. The excitation current calculation unit 102 may calculate the amplitude Idamp of the d-axis high frequency command current Idhref so that the amplitude of the harmonic current is 3% or more of the amplitude of the fundamental current.

[0035]

number

[0036] The d-axis deviation calculation unit 104 calculates the d-axis current deviation ΔId by subtracting the d-axis current Idr from the d-axis command current Idref. The q-axis deviation calculation unit 105 calculates the q-axis current deviation ΔIq by subtracting the q-axis current Iqr from the q-axis command current Iqref.

[0037] The d-axis current control unit 106 calculates a d-axis voltage command value Vdref based on the d-axis current deviation ΔId as a manipulated variable for feedback-controlling the d-axis current Idr to the d-axis command current Idref. The q-axis current control unit 107 calculates a q-axis voltage command value Vqref based on the q-axis current deviation ΔIq as a manipulated variable for feedback-controlling the q-axis current Iqr to the q-axis command current Iqref. In this embodiment, the feedback control of each of the current control units 106 and 107 is proportional-integral control.

[0038] The three-phase conversion unit 108 converts the d- and q-axis voltage command values ​​Vdref, Vqref in the two-phase rotating coordinate system into U-, V- and W-phase voltage command values ​​VUref, VVref, and VWref in the three-phase fixed coordinate system based on the d- and q-axis voltage command values ​​Vdref, Vqref and the electrical angle θe. The U-, V- and W-phase voltage command values ​​VUref, VVref, and VWref have waveforms with phases shifted by 120 degrees in electrical angle. The frequencies of the harmonic components included in the U-, V- and W-phase voltage command values ​​VUref, VVref, and VWref are set to frequencies near the first resonance frequency f1. The U-, V- and W-phase voltage command values ​​VUref, VVref, and VWref are composite voltages of a fundamental voltage corresponding to the fundamental current and a harmonic voltage corresponding to the harmonic current.

[0039] The signal generating unit 109 generates drive signals for the upper and lower arm switches SUp-SWn in the U, V and W phases based on the U, V and W phase voltage command values ​​VUref, VVref and VWref for passing the above-mentioned composite current through the stator winding 52. The generated drive signals are input to the gates of the respective switches. This executes switching control of the inverter 20. In this embodiment, the signal generating unit 109 corresponds to a "switch control unit."

[0040] As a result of switching control of inverter 20, a composite current in which harmonic current (see solid line in FIG. 6(b)) is superimposed on fundamental current (see FIG. 6(a)) flows through each phase winding 52U, 52V, 52W. The harmonic current flowing through stator winding 52 causes a field current to flow through field winding 70. FIG. 6(a) shows the progression of the fundamental current over one electrical angle period. The dashed dotted line in FIG. 6(b) shows the envelope of the harmonic current. The envelope of the harmonic current has the same period as the fundamental current. The values ​​on the vertical axis in FIG. 6 indicate the relative relationship between the magnitudes of the waveforms shown in FIGS. 6(a) and 6(b).

[0041] 7, the operating region of the rotating electric machine 40 is represented by the command torque Tref and the electrical angular velocity ωe of the rotor 60 (or the rotational speed of the rotor 60). The operating region is divided into a sinusoidal PWM control region, an overmodulation control region, and a square wave control region. The overmodulation control region is adjacent to the high speed side of the sinusoidal PWM control region.

[0042] When the control device 30 determines that the electrical angular velocity ωe calculated based on the electrical angle θe is less than the first speed threshold ωth1, it performs sinusoidal PWM control. The sinusoidal PWM control is switching control of the upper and lower arm switches for making each phase voltage applied to the stator windings 52 have a PWM voltage waveform when the peak value of each phase voltage applied to the stator windings 52 is equal to or less than the terminal voltage of the DC power supply 10. The first speed threshold ωth1 decreases as the command torque Tref increases.

[0043] When the control device 30 determines that the electrical angular velocity ωe is equal to or greater than the first speed threshold ωth1 and less than the second speed threshold ωth2, it performs overmodulation control. The overmodulation control is switching control of the upper and lower arm switches for making each phase voltage applied to the stator windings 52 into a PWM voltage waveform with a higher modulation rate than the PWM voltage waveform by sinusoidal PWM control when the peak value of each phase voltage applied to the stator windings 52 exceeds the terminal voltage of the DC power supply 10. The second speed threshold ωth2 becomes smaller as the command torque Tref becomes larger.

[0044] The control device 30 may determine whether the current operating point is in the overmodulation control region or the square wave control region based on the magnitude of the output voltage vector of the inverter 20, instead of using the first speed threshold value ωth1 and the second speed threshold value ωth2 as described above. The control device 30 may calculate the magnitude of the output voltage vector based on, for example, the following equation (eq2).

[0045] When the control device 30 determines that the operating point is in the overmodulation control region or the square wave control region, it performs field-weakening control to reduce the magnetic flux of the rotor 60. Hereinafter, the field-weakening control will be described with reference to a block diagram of the excitation current calculation unit 102 shown in FIG.

[0046] The excitation current calculation unit 102 functions as an "adjustment unit" and includes a voltage amplitude calculation unit 110, a voltage deviation calculation unit 111, and a feedback control unit 112. The voltage amplitude calculation unit 110 calculates a voltage amplitude Vom, which is the magnitude of the output voltage vector of the inverter 20 in a two-phase rotating coordinate system, based on the d-axis voltage command value Vdref calculated by the d-axis current control unit 106 and the q-axis voltage command value Vqref calculated by the q-axis current control unit 107. In detail, the voltage amplitude calculation unit 110 calculates the voltage amplitude Vom based on the following equation (eq2).

[0047]

number

[0048] The feedback control unit 112 calculates a deviation amount Xh, which is a manipulated variable for feedback-controlling the calculated voltage deviation ΔV to 0. In this embodiment, the feedback control used by the feedback control unit 112 is proportional-integral control.

[0049] The excitation current calculation unit 102 includes an excitation parameter calculation unit 113. The excitation parameter calculation unit 113 calculates the amplitude Idamp and the fluctuation frequency fh of the d-axis high frequency command current Idhref based on the calculated deviation amount Xh. The excitation parameter calculation unit 113 reduces the amplitude Idamp and the fluctuation frequency fh to reduce the excitation voltage component of the field winding 70, which is a voltage component included in the composite voltage. This reduces the magnetic flux of the rotor 60, and field weakening control is performed. The reason why the excitation voltage component can be reduced by reducing the amplitude Idamp and the fluctuation frequency fh will be described below.

[0050] The voltage equations of the motor in the two-phase rotating coordinate system are shown in the following equations (eq3) and (eq4). In the following equations (eq3) and (eq4), R is the resistance value of the stator winding 52, Ld and Lq are d-axis and q-axis inductances, and φ is the effective value of the interlinkage magnetic flux of the stator winding 52.

[0051]

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[0052]

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[0053]

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[0054]

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[0055] First, regarding the calculation method of the fluctuation frequency fh, when the deviation amount Xh is 0 or less, the excitation parameter calculation unit 113 sets the fluctuation frequency fh to the first frequency fa. When the deviation amount Xh is greater than 0 and less than the first threshold value Xth1, the excitation parameter calculation unit 113 sets the fluctuation frequency fh to a frequency higher than the second frequency fb (<fa) and lower than the first frequency fa, and the higher the deviation amount Xh, the lower the frequency. When the deviation amount Xh is greater than or equal to the first threshold value Xth1, the excitation parameter calculation unit 113 sets the fluctuation frequency fh to the second frequency fb.

[0056] Subsequently, regarding the calculation method of the amplitude Idamp, when the deviation amount Xh is less than or equal to the first threshold value Xth1, the excitation parameter calculation unit 113 sets the amplitude Idamp to the first amplitude Ia. When the deviation amount Xh is greater than the first threshold value Xth1 and less than the second threshold value Xth2 (>Xth1), the excitation parameter calculation unit 113 sets the amplitude Idamp to an amplitude greater than the second amplitude Ib (<Ia) and less than the first amplitude Ia, and the higher the deviation amount Xh, the smaller the amplitude. When the deviation amount Xh is greater than or equal to the second threshold value Xth2, the excitation parameter calculation unit 113 sets the amplitude Idamp to the second amplitude Ib.

[0057] When the amplitude Idamp is decreased, the torque reduction of the rotating electrical machine 40 increases. Therefore, in this embodiment, the deviation amount Xh at which the fluctuation frequency fh starts to decrease is set smaller than the deviation amount Xh at which the amplitude Idamp starts to decrease. As a result, prior to the reduction process of the amplitude Idamp, the magnetic flux of the rotor 60 can be reduced by the reduction process of the fluctuation frequency fh. As a result, the exciting current can be decreased while suppressing torque reduction.

[0058] Particularly in this embodiment, the amplitude Idamp starts to decrease when the deviation amount Xh exceeds a first threshold value Xth1, which is the deviation amount Xh at which the decrease in the variable frequency fh is completed. In other words, the decrease process of the amplitude Idamp starts when the deviation amount Xh does not become 0 or less even by the decrease process of the variable frequency fh. This makes it possible to decrease the field current while suitably suppressing the decrease in torque.

[0059] In this manner, the d-axis high-frequency command current Idhref is adjusted in the excitation current calculation section 102, and thus the excitation voltage component is adjusted.

[0060] 9 shows a flowchart of the field-weakening control process executed by the control device 30. This process is repeatedly executed at a predetermined control period, for example.

[0061] In step S10, the voltage amplitude calculation unit 110 calculates the voltage amplitude Vom based on the d-axis and q-axis voltage command values ​​Vdref and Vqref.

[0062] In step S11, the voltage deviation calculation unit 111 calculates a voltage deviation ΔV based on the calculated voltage amplitude Vom.

[0063] In step S12, feedback control section 112 calculates deviation amount Xh based on the calculated voltage deviation ΔV.

[0064] In step S13, the excitation parameter calculation unit 113 calculates the fluctuation frequency fh and the amplitude Idamp of the d-axis high-frequency command current Idhref based on the calculated deviation amount Xh.

[0065] In step S14, the d-axis high-frequency command current Idhref determined from the calculated fluctuation frequency fh and amplitude Idamp is calculated, and the calculated d-axis high-frequency command current Idhref is output to the superimposing unit 103.

[0066] As described above, in this embodiment, a self-excited field winding type rotating electric machine 40 is used. Therefore, there is no need to provide a power converter for energizing the field winding 70 in addition to the inverter 20. This allows the system to be simplified. In addition, field weakening control for reducing the magnetic flux of the rotor 60 in the high speed region is performed by the control device 30 that controls the torque of the rotating electric machine 40. Therefore, the field weakening control and the torque control can be realized by the common switching control of the inverter 20. This also contributes to the simplification of the system. In addition, the excitation voltage component is reduced by the switching control of the inverter 20, so that the output voltage of the inverter 20 can be reduced quickly.

[0067] <Modification of the first embodiment> The excitation parameter calculation unit 113 may vary only the fluctuation frequency fh of the fluctuation frequency fh and the amplitude Idamp based on the deviation amount Xh.

[0068] The excitation parameter calculation unit 113 may vary only the amplitude Idamp of the fluctuation frequency fh and the amplitude Idamp based on the deviation amount Xh. In this case, the excitation parameter calculation unit 113 may start to reduce the amplitude Idamp when the deviation amount Xh exceeds 0, similar to the manner in which the fluctuation frequency fh is reduced.

[0069] <Second embodiment> Hereinafter, the second embodiment will be described with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, the amplitude Idamp and the fluctuation frequency fh of the d-axis high frequency command current Idhref are calculated based on map information instead of the deviation amount Xh.

[0070] FIG. 10 is a block diagram showing the torque control process executed by the control device 30. As shown in FIG.

[0071] In the control device 30, the speed calculation unit 120 calculates the electrical angular speed ωe based on the electrical angle θe.

[0072] The excitation current calculation unit 121 functions as an "adjustment unit" and calculates the amplitude Idamp and fluctuation frequency fh of the d-axis high frequency command current Idhref based on the power supply voltage Vdc, the calculated electrical angular velocity ωe, the command torque Tref, and map information.

[0073] The map information is information in which the amplitude Idamp and the fluctuation frequency fh are defined in association with the power supply voltage Vdc, the electrical angular velocity ωe, and the command torque Tref (corresponding to the "judgment parameter"), and is stored in the storage unit of the control device 30. FIG. 11 shows an example of the map information. FIG. 11(A) shows the map information when the power supply voltage Vdc is the first voltage V1, FIG. 11(B) shows the map information when the power supply voltage Vdc is the second voltage V2 (>V1), and FIG. 11(C) shows the map information when the power supply voltage Vdc is the third voltage V3 (>V2). The relationships between the first frequency fa, the second frequency fb, the electrical angular velocity ωe, and the speed thresholds (ωth1, ωth2, ωth3) are similar to the relationships between the first frequency fa, the second frequency fb, the deviation amount Xh, and the first threshold Xth1 shown in FIG. 8 above.

[0074] Each map information includes information for the case where the command torque Tref is T1, T2, T3 (T1>T2>T3). The smaller the command torque Tref, the larger the speed thresholds (ωth1, ωth2, ωth3). The speed thresholds corresponding to T1, T2, T3 are ωth1, ωth2, ωth3.

[0075] Moreover, the higher the power supply voltage Vdc, the larger the speed thresholds (ωth1, ωth2, ωth3). In this manner, in the excitation current calculation section 121, the d-axis high frequency command current Idhref is adjusted, and therefore the excitation voltage component is adjusted.

[0076] 12 shows a flowchart of the field-weakening control process executed by the control device 30. This process is repeatedly executed at a predetermined control period, for example.

[0077] In step S20, the excitation current calculation unit 121 acquires the power supply voltage Vdc, the electrical angular velocity ωe, and the command torque Tref.

[0078] In step S21, the excitation current calculation unit 121 calculates the fluctuation frequency fh and the amplitude Idamp of the d-axis high frequency command current Idhref based on the acquired power supply voltage Vdc, electrical angular velocity ωe, and command torque Tref, and the map information.

[0079] In step S22, the d-axis high-frequency command current Idhref determined from the calculated fluctuation frequency fh and amplitude Idamp is calculated, and the calculated d-axis high-frequency command current Idhref is output to the superimposing unit 103.

[0080] According to the present embodiment described above, it is possible to achieve the same effects as the first embodiment.

[0081] <Modification of the second embodiment> The map information used by the excitation current calculation unit 121 may be information in which the amplitude Idamp and the fluctuation frequency fh are defined in association with one or two parameters of the power supply voltage Vdc, the electrical angular velocity ωe, and the command torque Tref.

[0082] <Third embodiment> Hereinafter, the third embodiment will be described with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, the U-, V-, and W-phase voltages VUr, VVr, and VWr detected by the voltage sensor 23 are used to calculate the voltage amplitude Vom, instead of the d- and q-axis voltage command values ​​Vdref and Vqref.

[0083] FIG. 13 is a block diagram of the excitation current calculation unit 102.

[0084] In the excitation current calculation unit 102, the voltage calculation unit 114 calculates the d- and q-axis voltages Vdr, Vqr based on the U-, V- and W-phase voltages VUr, VVr, and VWr detected by the voltage sensor 23 and the electrical angle θe. In detail, the voltage calculation unit 114 calculates the d- and q-axis voltages Vdr, Vqr based on the following equations (eq7) and (eq8).

[0085]

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[0086]

number

[0087]

number

[0088] <Fourth embodiment> The fourth embodiment will be described below with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, a method is used in which the excitation voltage component of the field winding 70 is reduced by increasing the d-axis current flowing through the stator winding 52. The reason why this method can be used will be described.

[0089] When the d-axis current is increased, the d-axis inductance Ld decreases due to the effect of magnetic saturation. In the term enclosed in braces on the right side of the above equation (eq5), the smaller the d-axis inductance Ld is, the smaller the excitation voltage component becomes. Therefore, by increasing the d-axis current, the excitation voltage component of the field winding 70 can be reduced.

[0090] FIG. 14 is a block diagram showing the torque control process executed by the control device 30. As shown in FIG.

[0091] The d-axis command calculation unit 125 calculates the d-axis base command current Idbref based on the command torque Tref. The d-axis command calculation unit 125 may calculate the d-axis base command current Idbref based on, for example, map information in which the command torque Tref and the d-axis base command current Idbref are associated with each other, and the input command torque Tref.

[0092] The inductance decreasing current calculation unit 130 functions as an "adjustment unit" and calculates an inductance decreasing current IdL, which is a d-axis current to be superimposed on the d-axis basic command current Idbref, based on the calculated d-axis and q-axis voltage command values ​​Vdref and Vqref. The inductance decreasing current IdL is a value of a DC component.

[0093] The first adder 122 calculates the sum of the d-axis basic command current Idbref and the inductance decreasing current IdL.

[0094] The second adder 123 calculates the d-axis command current Idref by adding the d-axis high-frequency command current Idhref calculated by the excitation current calculation unit 102 to the added value calculated by the first adder 122. The calculated d-axis command current Idref is input to the d-axis deviation calculation unit 104.

[0095] The q-axis command calculation unit 124 calculates the q-axis command current Iqref based on the command torque Tref and the additional value "Idbref+IdL" calculated by the first adder 122. The reason why the additional value is used in calculating the q-axis command current Iqref is that an appropriate q-axis current corresponding to the command torque Tref changes depending on the magnitude of the inductance decreasing current IdL. The q-axis command calculation unit 124 may calculate the q-axis command current Iqref based on, for example, map information in which the command torque Tref, the additional value, and the q-axis command current Iqref are associated with each other, and the input command torque Tref and the additional value. The calculated q-axis command current Iqref is input to the q-axis deviation calculation unit 105.

[0096] Next, the process of the inductance decreasing current calculation unit 130 will be described with reference to FIG.

[0097] The inductance decreasing current calculation unit 130 includes a voltage amplitude calculation unit 131, a voltage deviation calculation unit 132, and a feedback control unit 133. The voltage amplitude calculation unit 131 calculates the voltage amplitude Vom based on the d-axis and q-axis voltage command values ​​Vdref and Vqref, similar to the voltage amplitude calculation unit 110 in FIG.

[0098] The voltage deviation calculation unit 132 calculates the voltage deviation ΔV by subtracting the limit value Vlim from the calculated voltage amplitude Vom.

[0099] The feedback control unit 133 calculates a deviation amount Xh, which is a manipulated variable for feedback-controlling the calculated voltage deviation ΔV to 0. In this embodiment, the feedback control used by the feedback control unit 133 is proportional-integral control.

[0100] The inductance decreasing current calculation unit 130 includes a current value calculation unit 134. The current value calculation unit 134 calculates the inductance decreasing current IdL based on the calculated deviation amount Xh. In detail, when the deviation amount Xh is equal to or less than 0, the inductance decreasing current calculation unit 130 sets the inductance decreasing current IdL to 0.

[0101] When the deviation amount Xh is greater than 0 and less than the threshold value Xth, the current value calculation unit 134 sets the inductance decreasing current IdL to a value greater than 0 and smaller than the predetermined current IK (>0), and the greater the deviation amount Xh, the greater the value. When the deviation amount Xh is equal to or greater than the threshold value Xth, the current value calculation unit 134 sets the inductance decreasing current IdL to the predetermined current IK. In this way, the inductance decreasing current calculation unit 130 adjusts the inductance decreasing current IdL, and thus adjusts the excitation voltage component.

[0102] 16 shows a flowchart of the field-weakening control process executed by the control device 30. This process is executed repeatedly at a predetermined control period, for example.

[0103] In step S30, the voltage amplitude calculation unit 131 calculates the voltage amplitude Vom based on the d-axis and q-axis voltage command values ​​Vdref and Vqref.

[0104] In step S31, the voltage deviation calculation unit 132 calculates a voltage deviation ΔV based on the calculated voltage amplitude Vom.

[0105] In step S32, the feedback control unit 133 calculates the deviation amount Xh based on the calculated voltage deviation ΔV.

[0106] In step S33, the current value calculation unit 134 calculates the inductance decreasing current IdL based on the calculated deviation amount Xh.

[0107] In step S 34 , the calculated inductance decreasing current IdL is output to the first adder 122 .

[0108] According to the present embodiment described above, it is possible to achieve effects similar to those of the first embodiment.

[0109] <Fifth embodiment> Hereinafter, the fifth embodiment will be described with reference to the drawings, focusing on the differences from the first embodiment. The control device 30 of this embodiment repeatedly executes a process of calculating the amplitude Idamp and the fluctuation frequency fh of the d-axis high frequency command current Idhref that can make the voltage amplitude Vom equal to or less than the limit value Vlim within one control period.

[0110] 17 shows a flowchart of the field-weakening control process executed by the control device 30. This process is executed repeatedly at a predetermined control period, for example.

[0111] In step S40, the d-axis command current Idref is calculated based on the d-axis basic command current Idbref and the d-axis high-frequency command current Idhref in the command current calculation unit 101, the excitation current calculation unit 102, and the superimposition unit 103. Also, the command current calculation unit 101 calculates the d-axis command current Idref.

[0112] In step S41, the d- and q-axis deviation calculation units 104 and 105 and the d- and q-axis current control units 106 and 107 calculate the d- and q-axis voltage command values ​​Vdref and Vqref based on the d- and q-axis command currents Idref and Iqref calculated in step S40.

[0113] In step S42, the excitation current calculation unit 102 calculates the voltage amplitude Vom based on the calculated d-axis and q-axis voltage command values ​​Vdref and Vqref.

[0114] In step S43, the excitation current calculation unit 102 determines whether the calculated voltage amplitude Vom is equal to or greater than the limit value Vlim.

[0115] If it is determined in step S43 that the voltage amplitude Vom is less than the limit value Vlim, the process proceeds to step S44. In step S44, the three-phase conversion unit 108 calculates U-, V-, and W-phase voltage command values ​​VUref, VVref, and VWref based on the d- and q-axis voltage command values ​​Vdref, Vqref calculated in step S41 and the electrical angle θe.

[0116] In step S45, signal generating unit 109 generates drive signals for upper and lower arm switches SUp to SWn in the U, V and W phases based on the calculated U, V and W phase voltage command values ​​VUref, VVref and VWref.

[0117] On the other hand, if it is determined in step S43 that the voltage amplitude Vom is equal to or greater than the limit value Vlim, the process proceeds to step S46. In step S46, the excitation current calculation unit 102 performs at least one of a process of decreasing the amplitude Idamp of the current d-axis high frequency command current Idhref and a process of lowering the fluctuation frequency fh of the current d-axis high frequency command current Idhref. For example, after starting the process of FIG. 17, when a positive determination is made for the first time in step S43, the current amplitude Idamp and fluctuation frequency fh are the amplitude Idamp and fluctuation frequency fh used in step S40. On the other hand, when a negative determination is made in step S50, which will be described later, the current amplitude Idamp and fluctuation frequency fh are the amplitude Idamp and fluctuation frequency fh used in the most recent step S47.

[0118] In the following step S47, the command current calculation unit 101, the excitation current calculation unit 102, and the superimposition unit 103 calculate the d-axis command current Idref based on the d-axis base command current Idbref and the d-axis high frequency command current Idhref. The amplitude Idamp and the fluctuation frequency fh of the d-axis high frequency command current Idhref used here are the amplitude Idamp and the fluctuation frequency fh calculated in the most recent step S46. Also, the command current calculation unit 101 calculates the d-axis command current Idref.

[0119] In step S48, the d- and q-axis error calculation units 104 and 105 and the d- and q-axis current control units 106 and 107 calculate the d- and q-axis voltage command values ​​Vdref and Vqref based on the d- and q-axis command currents Idref and Iqref calculated in step S47.

[0120] In step S49, the excitation current calculation section 102 calculates the voltage amplitude Vom based on the d-axis and q-axis voltage command values ​​Vdref and Vqref calculated in the most recent step S48.

[0121] In step S50, the excitation current calculation unit 102 determines whether or not the voltage amplitude Vom calculated in the most recent step S49 is equal to or smaller than the limit value Vlim.

[0122] When it is determined in step S50 that the voltage amplitude Vom exceeds the limit value Vlim, the process proceeds to step S46. As a result, the excitation current calculation unit 102 performs at least one of the process of decreasing the current amplitude Idamp and the process of lowering the current variable frequency fh again.

[0123] On the other hand, if it is determined in step S50 that the voltage amplitude Vom is equal to or less than the limit value Vlim, the process proceeds to step S44. In step S44, the three-phase conversion unit 108 calculates U-, V-, and W-phase voltage command values ​​VUref, VVref, and VWref based on the d- and q-axis voltage command values ​​Vdref, Vqref calculated in the most recent step S48 and the electrical angle θe.

[0124] According to the present embodiment described above, the calculation of the d- and q-axis voltage command values ​​Vdref, Vqref that can make the voltage amplitude Vom equal to or smaller than the limit value Vlim can be completed within one control cycle of the control device 30.

[0125] Sixth embodiment The sixth embodiment will be described below with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, the d, q-axis current control units 106, 107 change the feedback gain of the feedback control when the amplitude Idamp of the d-axis high-frequency command current Idhref is large, more than when the amplitude Idamp is small. This change process is performed in consideration of the fact that the inductance of the rotating electric machine 40 decreases when the amplitude Idamp is large.

[0126] 18 and 19, the d-axis current control unit 106 increases the proportional gain Kpd and the integral gain Kid in the proportional-integral control as the amplitude Idamp increases. For example, the d-axis current control unit 106 may increase the proportional gain Kpd and the integral gain Kid stepwise or continuously as the amplitude Idamp increases.

[0127] The q-axis current control unit 107 increases the proportional gain Kpq and the integral gain Kiq in the proportional-integral control as the amplitude Idamp increases. For example, the q-axis current control unit 107 may increase the proportional gain Kpq and the integral gain Kiq stepwise or continuously as the amplitude Idamp increases.

[0128] According to the present embodiment described above, even if the inductance of the rotary electric machine 40 changes due to a change in the magnitude of the current, the responsiveness of the current control can be maintained at a high level.

[0129] Seventh embodiment The seventh embodiment will be described below with reference to the drawings, focusing on the differences from the sixth embodiment. In this embodiment, the d-axis and q-axis current control units 106 and 107 use the magnitude of the d-axis basic command current Idbref and the magnitude of the q-axis command current Iqref instead of the magnitude of the amplitude Idamp of the d-axis high-frequency command current Idhref.

[0130] 20 and 21, the d-axis current control unit 106 increases the proportional gain Kpd and the integral gain Kid in the proportional-integral control as the d-axis base command current Idbref and the q-axis command current Iqref increase. The q-axis current control unit 107 increases the proportional gain Kpq and the integral gain Kiq in the proportional-integral control as the d-axis base command current Idbref and the q-axis command current Iqref increase.

[0131] According to the present embodiment described above, even if the inductance of the rotary electric machine 40 changes due to a change in the magnitude of the current, the responsiveness of the current control can be maintained at a high level.

[0132] <Other embodiments> Each of the above embodiments may be modified as follows.

[0133] The high-frequency current (specifically, high-frequency excitation current) passed through the stator winding 52 is not limited to a harmonic current whose fluctuating frequency is N times (N is an integer equal to or greater than 2) the frequency of the fundamental current, but may be a current whose fluctuating frequency is other than N times the frequency of the fundamental current as long as the fluctuating frequency is higher than the frequency of the fundamental current.

[0134] The second winding portion 71b may be disposed closer to the stator 50 in the radial direction than the first winding portion 71a.

[0135] The capacitor 81 that constitutes the resonant circuit of the rotor 60 may be electrically connected in parallel to the first winding portion 71a instead of the second winding portion 71b.

[0136] The capacitor 81 does not have to be provided in the resonant circuit of the rotor 60.

[0137] The rotating electric machine is not limited to an inner rotor type rotating electric machine, but may be an outer rotor type rotating electric machine. In this case, the main pole portion protrudes radially inward from the rotor core.

[0138] The rotating electric machine is not limited to a star-connected rotating electric machine, but may be a delta-connected rotating electric machine.

[0139] In the first embodiment, the stator core may not be provided with teeth.

[0140] The rotating electric machine is not limited to a rotating electric machine used as an in-vehicle main engine, but may be, for example, a rotating electric machine used as an ISG (Integrated Starter Generator) that serves as both a motor and a generator.

[0141] The moving body on which the control system is mounted is not limited to a vehicle, but may be, for example, an aircraft or a ship. Furthermore, the control system is not limited to a system mounted on a moving body, but may be a stationary system.

[0142] The control device and the method described in the present disclosure may be realized by a special-purpose computer provided by configuring a processor and a memory programmed to execute one or more functions embodied in a computer program. Alternatively, the control device and the method described in the present disclosure may be realized by a special-purpose computer provided by configuring a processor with one or more dedicated hardware logic circuits. Alternatively, the control device and the method described in the present disclosure may be realized by one or more special-purpose computers configured by a combination of a processor and a memory programmed to execute one or more functions and a processor configured with one or more hardware logic circuits. In addition, the computer program may be stored in a computer-readable non-transitory tangible recording medium as instructions executed by the computer. [Explanation of symbols]

[0143] 20... inverter, 30... control device, 40... rotating electric machine, 50... stator, 52... stator winding, 60... rotor, 70... field winding.

Claims

1. A rotating electric machine (40) having a stator (50) including a stator winding (52) and a rotor (60) including a field winding (70); an inverter (20) electrically connected to the stator winding; A control device (30) for a rotating electric machine applied to a system including: The rotating electric machine is configured such that a high-frequency voltage is applied to the stator winding to induce a voltage in the field winding, causing a field current to flow, a switch control unit (109) that performs switching control of the inverter so as to apply a composite voltage of the high frequency voltage and a fundamental wave voltage having a frequency lower than that of the high frequency voltage to the stator winding; an adjustment unit (102, 121, 130) that performs an adjustment process to adjust a voltage component included in the composite voltage, which is an excitation voltage component of the field winding, so that an output voltage (Vom) of the inverter is equal to or lower than a limit value (Vlim); A control device for a rotating electric machine comprising:

2. 2. The control device for a rotating electric machine according to claim 1, wherein, as the adjustment process, the adjustment unit (102) performs a process of lowering the frequency of the high-frequency voltage so that the output voltage of the inverter becomes equal to or lower than the limit value when the output voltage of the inverter reaches the limit value.

3. 2. The control device for a rotating electric machine according to claim 1, wherein, as the adjustment process, the adjustment unit (102) performs a process of reducing an amplitude of the high-frequency voltage so that the output voltage of the inverter becomes equal to or lower than the limit value when the output voltage of the inverter reaches the limit value.

4. The adjustment unit performs the adjustment process as follows: When the output voltage of the inverter reaches the limit value, a process of reducing the frequency of the high frequency voltage so that the output voltage of the inverter becomes equal to or lower than the limit value; a process of reducing an amplitude of the high frequency voltage when an output voltage of the inverter exceeds the limit value after the frequency of the high frequency voltage is reduced; The control device for a rotating electric machine according to claim 2 , further comprising:

5. The system includes a current sensor (21) that detects a current flowing through the stator winding; a two-phase conversion unit (100) that converts the current of the stator winding in a three-phase fixed coordinate system of the rotating electric machine into d-axis and q-axis currents (Idr, Iqr) in a two-phase rotating coordinate system of the rotating electric machine based on the detection value of the current sensor; a superposition unit (103) that calculates a d-axis command current (Idref) by superimposing a d-axis high-frequency command current (Idhref), which is an AC component corresponding to the high-frequency voltage, on a d-axis fundamental command current (Idbref), which is a DC component corresponding to the fundamental wave voltage; a d-axis current control unit (106) that calculates a d-axis voltage command value (Vdref) to be applied to the stator winding in order to control the converted d-axis current to the d-axis command current; a q-axis current control unit (107) that calculates a q-axis voltage command value (Vqref) to be applied to the stator winding in order to control the converted q-axis current to a q-axis command current (Iqref); Equipped with The switch control unit performs the switching control based on the calculated d-axis and q-axis voltage command values. The adjustment unit is Calculating a voltage amplitude (Vom), which is a magnitude of an output voltage vector of the inverter, based on the calculated d-axis and q-axis voltage command values; 3. The control device for a rotating electric machine according to claim 2, wherein, in the adjustment process, if the calculated voltage amplitude becomes equal to or greater than the limit value, a frequency of the high-frequency voltage is reduced so that a deviation between the calculated voltage amplitude and the limit value approaches zero.

6. The system includes a current sensor (21) that detects a current flowing through the stator winding; a two-phase conversion unit (100) that converts the current of the stator winding in a three-phase fixed coordinate system of the rotating electric machine into d-axis and q-axis currents (Idr, Iqr) in a two-phase rotating coordinate system of the rotating electric machine based on the detection value of the current sensor; a superposition unit (103) that calculates a d-axis command current (Idref) by superimposing a d-axis high-frequency command current (Idhref), which is an AC component corresponding to the high-frequency voltage, on a d-axis fundamental command current (Idbref), which is a DC component corresponding to the fundamental wave voltage; a d-axis current control unit (106) that calculates a d-axis voltage command value (Vdref) to be applied to the stator winding in order to control the converted d-axis current to the d-axis command current; a q-axis current control unit (107) that calculates a q-axis voltage command value (Vqref) to be applied to the stator winding in order to control the converted q-axis current to a q-axis command current (Iqref); Equipped with The switch control unit performs the switching control based on the calculated d-axis and q-axis voltage command values. The adjustment unit is Calculating a voltage amplitude (Vom), which is a magnitude of an output voltage vector of the inverter, based on the calculated d-axis and q-axis voltage command values; 4. The control device for a rotating electric machine according to claim 3, wherein, in the adjustment process, if the calculated voltage amplitude becomes equal to or greater than the limit value, the amplitude of the high-frequency voltage is reduced so that a deviation between the calculated voltage amplitude and the limit value approaches zero.

7. The system includes a voltage sensor (23) for detecting an output voltage of each phase of the inverter; The adjustment unit (102) Calculating a voltage amplitude (Vom) which is a magnitude of an output voltage vector of the inverter based on a detection value of the voltage sensor; 3. The control device for a rotating electric machine according to claim 2, wherein, in the adjustment process, if the calculated voltage amplitude becomes equal to or greater than the limit value, a frequency of the high-frequency voltage is reduced so that a deviation between the calculated voltage amplitude and the limit value approaches zero.

8. The system includes a voltage sensor (23) for detecting an output voltage of each phase of the inverter; The adjustment unit (102) Calculating a voltage amplitude (Vom) which is a magnitude of an output voltage vector of the inverter based on a detection value of the voltage sensor; 4. The control device for a rotating electric machine according to claim 3, wherein, in the adjustment process, if the calculated voltage amplitude becomes equal to or greater than the limit value, the amplitude of the high-frequency voltage is reduced so that a deviation between the calculated voltage amplitude and the limit value approaches zero.

9. The adjustment unit (121) performs the adjustment process as follows:

2. The control device for a rotating electric machine according to claim 1, wherein a process is performed to calculate a d-axis high frequency command current (Idhref), which is an AC component corresponding to the high frequency voltage, based on map information in which a determination parameter is at least one of a power supply voltage (Vdc) of the inverter, an electrical angular velocity (ωe) of the rotor, and a command torque (Tref) of the rotating electric machine, and an amplitude and a fluctuation frequency of the d-axis high frequency command current (Idhref).

10. 2. The control device for a rotating electric machine according to claim 1, wherein, as the adjustment process, the adjustment unit (130) performs a process of increasing a d-axis current (IdL) flowing through the stator winding when the output voltage of the inverter reaches the limit value so that the output voltage of the inverter becomes equal to or lower than the limit value.

11. The system includes a current sensor (21) that detects a current flowing through the stator winding; the switch control unit generates a drive signal for the inverter for applying the composite voltage to the stator winding for each control period; 2. The control device for a rotating electric machine according to claim 1, wherein the adjustment unit (102) performs, as the adjustment process, a process of repeatedly calculating a d-axis high-frequency command current (Idhref) of an AC component corresponding to the high-frequency voltage within one control period so that the output voltage of the inverter is equal to or lower than the limit value.

12. The system includes a current sensor (21) that detects a current flowing through the stator winding; a two-phase conversion unit (100) that converts the current of the stator winding in a three-phase fixed coordinate system of the rotating electric machine into d-axis and q-axis currents (Idr, Iqr) in a two-phase rotating coordinate system of the rotating electric machine based on the detection value of the current sensor; a superposition unit (103) that calculates a d-axis command current (Idref) by superimposing a d-axis high-frequency command current (Idhref), which is an AC component corresponding to the high-frequency voltage, on a d-axis fundamental command current (Idbref), which is a DC component corresponding to the fundamental wave voltage; a d-axis current control unit (106) that calculates a d-axis voltage command value (Vdref) to be applied to the stator winding in order to feedback control the converted d-axis current to the d-axis command current; a q-axis current control unit (107) that calculates a q-axis voltage command value (Vqref) to be applied to the stator winding in order to feedback control the converted q-axis current to a q-axis command current (Iqref); Equipped with The switch control unit performs the switching control based on the calculated d-axis and q-axis voltage command values.

12. The control device for a rotating electric machine according to claim 1, wherein the d, q axes current control unit changes a feedback gain of the feedback control based on the magnitude of the amplitude of the d axis high frequency command current.

13. The system includes a current sensor (21) that detects a current flowing through the stator winding; a two-phase conversion unit (100) that converts the current of the stator winding in a three-phase fixed coordinate system of the rotating electric machine into d-axis and q-axis currents (Idr, Iqr) in a two-phase rotating coordinate system of the rotating electric machine based on the detection value of the current sensor; a superposition unit (103) that calculates a d-axis command current (Idref) by superimposing a d-axis high-frequency command current (Idhref), which is an AC component corresponding to the high-frequency voltage, on a d-axis fundamental command current (Idbref), which is a DC component corresponding to the fundamental wave voltage; a d-axis current control unit (106) that calculates a d-axis voltage command value (Vdref) to be applied to the stator winding in order to feedback control the converted d-axis current to the d-axis command current; a q-axis current control unit (107) that calculates a q-axis voltage command value (Vqref) to be applied to the stator winding in order to feedback control the converted q-axis current to a q-axis command current (Iqref); Equipped with The switch control unit performs the switching control based on the calculated d-axis and q-axis voltage command values. the d-axis current control unit calculates the d-axis voltage command value to be applied to the stator winding in order to feedback control the converted d-axis current to the d-axis command current; the q-axis current control unit calculates the q-axis voltage command value to be applied to the stator winding in order to feedback control the converted q-axis current to the q-axis command current; 12. The control device for a rotating electric machine according to claim 1, wherein the d, q axes current control unit changes a feedback gain of the feedback control based on a magnitude of an amplitude of the fundamental wave voltage.

14. The rotor has a rotor core (61) and main pole portions (62) provided at predetermined intervals in the circumferential direction and protruding in the radial direction from the rotor core, The field winding has a first winding portion (71a) and a second winding portion (71b) electrically connected in series, The first winding portion and the second winding portion are wound around the respective main pole portions, The rotor is a diode (80) electrically connected in parallel to the series connection of the first winding portion and the second winding portion; a capacitor (81) electrically connected in parallel to either the first winding portion or the second winding portion; The control device for a rotating electric machine according to any one of claims 1 to 11, comprising:

15. A rotating electric machine (40) having a stator (50) including a stator winding (52) and a rotor (60) including a field winding (70); an inverter (20) electrically connected to the stator winding; A computer (31); In a program applied to a system comprising: The rotating electric machine is configured such that a high-frequency voltage is applied to the stator winding to induce a voltage in the field winding, causing a field current to flow, The computer includes: A process of performing switching control of the inverter so as to apply a composite voltage of the high frequency voltage and a fundamental wave voltage having a frequency lower than that of the high frequency voltage to the stator winding; an adjustment process for adjusting an excitation voltage component of the field winding, which is a voltage component included in the composite voltage, so that an output voltage (Vom) of the inverter is equal to or lower than a limit value (Vlim); A program to execute.

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