Epsilon-near-zero metamaterial antenna and design method therefor

Abstract

The present application relates to the technical field of communications, and in particular to an epsilon-near-zero metamaterial antenna and a design method therefor. The epsilon-near-zero metamaterial antenna comprises a first radiator, a second radiator and a metamaterial structure; the metamaterial structure is arranged between the first radiator and the second radiator; the metamaterial structure comprises a plurality of metamaterial units; each metamaterial unit is composed of a dielectric unit and a metal wire unit; and the metamaterial structure is used for generating electric resonance in a preset direction, so as to achieve a target near-zero dielectric constant in a preset communication frequency band. According to the epsilon-near-zero metamaterial antenna of the present application, by arranging the metamaterial structure between the first radiator and the second radiator, isolation between the first radiator and the second radiator is increased, thereby reducing coupling between the first radiator and the second radiator, especially in a near field.

Description

A near-zero dielectric constant metamaterial antenna and its design method Technical Field

[0001] The present application relates to the field of communication technology, and in particular to a near-zero dielectric constant metamaterial antenna and a design method thereof. Background Art

[0002] Antennas are devices that radiate or receive electromagnetic waves into space and are an indispensable part of communication systems. Modern radio communications, broadcasting, navigation, electronic countermeasures, remote sensing, and other engineering systems all rely on antennas to transmit or receive electromagnetic waves to transmit information. However, antennas composed of symmetrically placed metal conductors, where the two ends of the conductors are close to each other, are fed separately. Due to their excellent radiation performance, coupling between the two sides becomes one of the main sources of interference, especially in the near field. Coupling also affects radiation performance and reduces communication efficiency. Common decoupling methods in the prior art include increasing the spacing between antennas and using metal isolation plates. However, increasing the spacing will increase the size of the device to a certain extent, which is not conducive to integration, and the use of isolation plates will affect the radiation performance of the antenna itself.

[0003] Summary of the Invention

[0004] Based on the above technical problems, the present application aims to provide a near-zero dielectric constant metamaterial antenna to solve the problem of coupling affecting the antenna radiation performance.

[0005] In a first aspect, the present application provides a near-zero dielectric constant metamaterial antenna, which includes a first radiator, a second radiator, and a metamaterial structure; the metamaterial structure is arranged between the first radiator and the second radiator; the metamaterial structure includes a plurality of metamaterial units, each metamaterial unit is composed of a dielectric unit and a metal wire unit, and the metamaterial structure is used to generate electric resonance in a preset direction to achieve a target near-zero dielectric constant in a preset communication frequency band.

[0006] In some embodiments of the present application, the first radiator includes a first conductor and a first feeding structure connected to the first conductor, the second radiator includes a second conductor and a second feeding structure connected to the second conductor, and the first radiator and the second radiator are both used to send communication data and / or receive communication data.

[0007] In some embodiments of the present application, the metal wire unit includes one or more groups of metal wires with preset widths; each metamaterial unit is composed of a dielectric unit and a metal wire unit, including:

[0008] The one or more groups of metal wires with preset widths are mounted on the base surface of the dielectric unit.

[0009] In some embodiments of the present application, the metal wire unit is a group of metal wires attached to the central area of ​​the substrate surface of the dielectric unit;

[0010] The metal wire unit comprises a plurality of groups of metal wires, and a preset distance exists between each group of metal wires.

[0011] In some embodiments of the present application, each group of metal wires has a multi-bend structure.

[0012] In some embodiments of the present application, the multi-bending structure is obtained by bending the metal wire multiple times by 90 degrees on the base surface of the dielectric unit.

[0013] In some embodiments of the present application, a first supporting structure is further connected between the first radiator and the metamaterial structure.

[0014] In some embodiments of the present application, a second supporting structure is further connected between the metamaterial structure and the second radiator.

[0015] In some embodiments of the present application, the target near-zero dielectric constant is a real number or a complex number. If the target near-zero dielectric constant is a complex number, the real part of the target near-zero dielectric constant is a real number between -1 and 1.

[0016] A second aspect of the present application provides a design method for a near-zero dielectric constant metamaterial antenna as described in any one of the embodiments of the present application, the design method comprising:

[0017] Obtaining an ideal medium, and simulating a near-zero dielectric constant metamaterial antenna using the ideal medium;

[0018] The degree of optimization of the target near-zero dielectric constant to the decoupling performance of the near-zero dielectric constant metamaterial antenna is determined according to the simulation results.

[0019] The technical solutions provided in the embodiments of this application have at least the following technical effects or advantages:

[0020] The near-zero dielectric constant metamaterial antenna in each embodiment of the present application increases the isolation between the first and second radiators while barely affecting the radiation characteristics of the first and second radiators by disposing a metamaterial structure between them, thereby reducing the coupling between the first and second radiators, especially in the near field. In particular, the metamaterial structure includes multiple metamaterial units, each of which is composed of a dielectric unit and a metal wire unit. The metamaterial structure is configured to generate electrical resonance in a preset direction, thereby reducing the dielectric constant of the dielectric unit to near zero, thereby achieving a target near-zero dielectric constant. Simulations of the near-zero dielectric constant metamaterial antenna demonstrate that the target near-zero dielectric constant optimizes the decoupling performance of the near-zero dielectric constant metamaterial antenna.

[0021] It should be understood that the foregoing general description and the following detailed description are exemplary and explanatory only and are not restrictive of the present application. BRIEF DESCRIPTION OF THE DRAWINGS

[0022] Various other advantages and benefits will become apparent to those skilled in the art upon reading the detailed description of the preferred embodiment below. The accompanying drawings are for illustration purposes only and are not to be considered as limiting the present application. The same reference symbols are used throughout the drawings to represent the same components. In the drawings:

[0023] FIG1 shows a schematic structural diagram of a near-zero dielectric constant metamaterial antenna in the prior art;

[0024] FIG2 shows a schematic diagram of a metamaterial structure in an exemplary embodiment of the present application;

[0025] FIG3 shows a schematic diagram of radiation of an electric dipole antenna in the near field in an exemplary embodiment of the present application;

[0026] FIG4 is a schematic diagram showing a near-zero dielectric constant metamaterial antenna technology effect curve in an exemplary embodiment of the present application;

[0027] FIG5 shows a schematic diagram of an ideal medium in an exemplary embodiment of the present application;

[0028] FIG6 shows a schematic diagram of an analysis of the effects of various parameters on the isolation between two radiators in a near-zero dielectric constant metamaterial antenna;

[0029] FIG7 shows another schematic diagram of analyzing the effects of various parameters on the isolation between two radiators in a near-zero dielectric constant metamaterial antenna;

[0030] FIG8 shows a schematic structural diagram of an electronic device provided by an exemplary embodiment of the present application.

[0031] It should be understood that the foregoing general description and the following detailed description are exemplary and explanatory only and are not restrictive of the present application. DETAILED DESCRIPTION

[0032] The present application will be further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the embodiments described herein are only used to explain the relevant invention and are not intended to limit the invention. It should also be noted that for ease of description, only the parts relevant to the relevant invention are shown in the accompanying drawings.

[0033] An antenna composed of symmetrically placed metal conductors, such as a dipole antenna. Dipole antennas have always been the earliest, simplest, and most widely used type of antenna in communication systems. The two ends of the dipole antenna conductors are close to each other and are fed separately. Due to its excellent radiation performance, the coupling between the two sides becomes one of the main sources of interference, especially in the near field, and the coupling affects the radiation performance and reduces communication efficiency. Common decoupling methods in the prior art include increasing the distance between the two poles of the dipole antenna and using a metal isolation plate. However, increasing the distance will increase the size of the device to a certain extent, which is not conducive to integration, and the use of an isolation plate will affect the radiation performance of the antenna itself.

[0034] Therefore, in some embodiments of the present application, a near-zero dielectric constant metamaterial antenna is provided. Referring to FIG1 , the near-zero dielectric constant metamaterial antenna includes a first radiator, a second radiator, and a metamaterial structure. The metamaterial structure is disposed between the first radiator and the second radiator to isolate the first radiator from the second radiator. The metamaterial structure includes a plurality of metamaterial units, each of which is composed of a dielectric unit and a metal wire unit. The metamaterial structure is configured to generate electrical resonance in a preset direction to achieve a target near-zero dielectric constant in a preset communication frequency band. The preset direction here can be the z-axis direction. The first radiator includes a first conductor and a first feeding structure connected to the first conductor, and the second radiator includes a second conductor and a second feeding structure connected to the second conductor. The first radiator and the second radiator are both configured to transmit and / or receive communication data. As shown in FIG1 , the distance between the two radiators is d, and the lengths of the first conductor and the second conductor are equal, both being l, where l and d are both greater than 0 and l is less than d.

[0035] In one specific implementation, the dielectric unit is a dielectric substrate, which is a type of PCB board commonly used in the industry. The dielectric constant of the dielectric substrate is preferably 2.2, but substrates with other dielectric constants can also be used. The dielectric constant of the dielectric substrate can be selected based on actual needs. However, if a dielectric substrate with a dielectric constant of 2.2 is used in a specific implementation, 2.2 is not a near-zero dielectric constant, so metal wires need to be mounted on the surface of the dielectric substrate to reduce the dielectric constant of the metamaterial unit. Specifically, the metal wire unit includes one or more groups of metal wires of a preset width; each metamaterial unit is composed of a dielectric unit and a metal wire unit, including: one or more groups of metal wires of a preset width mounted on the substrate surface of the dielectric unit. The metal wire unit is a group of metal wires mounted in the center area of ​​the substrate surface of the dielectric unit; the metal wire unit is a plurality of groups of metal wires, each group of metal wires having a preset distance between them, and the preset distance is determined by the shape and size of the dielectric substrate. Optionally, the shape of the metamaterial unit can be rectangular, cylindrical, convex lens, etc.

[0036] In a specific implementation, referring to FIG2 , each group of metal wires is a multiple-bend structure. FIG2(a) shows the three-dimensional structure of a metamaterial unit, FIG2(b) shows the cross-section of a metamaterial unit, and FIG2(c) shows the three-dimensional structure of multiple metamaterial units. As shown in FIG2(a), the thickness of a metamaterial unit is tm. As shown in FIG2(b) and FIG2(c), the width of the dielectric substrate of the metamaterial unit is a, the side length of the bent metal wire is b, the spacing is w1, and the line width is w2. As shown in FIG2(c), the interval between the metamaterial units is py, and the distance occupied by the bent structure composed of each group of metal wires on the x-axis is px. The multiple-bend structure is obtained by bending the metal wires 90 degrees multiple times on the substrate surface of the dielectric unit. During specific mounting, a preferred mounting method is as follows: for any set of metal wires of a preset width, the set of metal wires of the preset width are mounted on the surface of a dielectric substrate along a first direction for a complete first distance; the portion of the metal wires of the preset width remaining after the first distance is bent in a second direction, and the set of metal wires of the preset width are mounted on the surface of the dielectric substrate along the second direction for a complete second distance; the portion of the metal wires of the preset width remaining after the first and second distances is bent in a third direction, and the set of metal wires of the preset width are mounted on the surface of the dielectric substrate along the third direction for a complete third distance; and the mounting steps along the first, second, and third directions are repeated until the set of metal wires of the preset width are mounted; wherein the first direction is perpendicular to the second direction, the first direction is opposite to the second direction, and the first distance is equal to the third distance. The multi-bend structure produced by this mounting method is a rectangular wave structure. However, rounding the corners at the bends of the metal wires is also acceptable. The multi-bend structure generates electrical resonance in the preset direction, achieving the target near-zero dielectric constant in the preset communication frequency band, and also enabling miniaturization of the unit, thereby facilitating integration.

[0037] In some embodiments of the present application, a first supporting structure is further connected between the first radiator and the metamaterial structure. A second supporting structure is further connected between the metamaterial structure and the second radiator. The first radiator including the first feeding structure, the metamaterial structure, and the second radiator including the second feeding structure are connected or integrated into one through the two supporting structures, wherein a supporting structure can also be provided between multiple metamaterial units, and the two radiators are fed through the feeding structure to receive or send signals. The target near-zero dielectric constant is a real number or a complex number. If the target near-zero dielectric constant is a complex number, the real part of the target near-zero dielectric constant is a real number between -1 and 1. The application of near-zero dielectric constant materials increases the isolation between two radiators, such as dipole antennas, so that the interference between the two radiators in the near field, i.e., the coupling, is reduced. Specifically, the radiation of an electric dipole antenna in the near field is taken as an example. The radiation field of a half-wavelength electric dipole antenna in the near field is expressed by the following formula:

[0038] In the above formula, referring to Figure 3, E r , E θ and H Φ The expression of the three-dimensional components of the electric field at a point in the near field is represented by I0, where I0 represents the current amplitude in the dipole, L represents the length of the dipole, ω represents the angular frequency of the dipole oscillation, t represents time, r represents the distance from the point to the center of the dipole, c represents the speed of light, ε0 represents the dielectric constant of vacuum, and θ represents the angle between the r direction and the z axis at the point. The radiation of the electric dipole in the near field is different from that in the far field, because r is relatively small in the near field, so the radiation of the dipole E r This item cannot be ignored. r Affected by the two parameters r and θ, the closer θ is to 0, the smaller r is, and E r The intensity of the antenna is greater, which is specifically manifested as an evanescent field along the r direction, which decays rapidly as r increases. In the case described in this embodiment, since θ is almost 0 and the interval d between the two antennas is very small, the coupling between the antennas is mainly affected by E. r The influence of the component, and the use of near-zero dielectric constant materials can weaken the E reaching the other dipole. r 4, in the operating frequency range of 3.3GHz-3.7GHz, the dipole antenna has an input end reflection coefficient amplitude of less than -10dB |S 11 When the near-zero dielectric constant metamaterial is added between the dipoles, S 21 The amplitude of the input end reflection coefficient|S is lower than that without the near-zero dielectric constant metamaterial, and the input end reflection coefficient|S11 Within the 3.3GHz-3.7GHz operating bandwidth, the difference is still less than -10dB. This shows that the near-field interference between the two radiators, or the coupling, is reduced.

[0039] In some embodiments of the present application, a design method for a near-zero dielectric constant metamaterial antenna as described in any of the embodiments of the present application is also provided to verify the isolation or decoupling performance of the near-zero dielectric constant metamaterial antenna. The design method includes: obtaining an ideal medium, and simulating a near-zero dielectric constant metamaterial antenna through the ideal medium; and determining the degree of optimization of the target near-zero dielectric constant on the decoupling performance of the near-zero dielectric constant metamaterial antenna based on the simulation results. As shown in FIG5 , the ideal medium is cylindrical, with a radius of r, a height of h, and relative dielectric constants and relative magnetic permeabilities of ε and ε, respectively. r and μ r The simulation process needs to analyze the influence of various parameters on the isolation of the radiator. First, analyze the influence of dielectric constant on isolation. Let μ of ideal medium be r =1, h = 13.34 mm, r = 26.69 mm, in the frequency range of 3.2 GHz - 3.8 GHz | S 21 |With ε r The change of is shown in Figure 6. As can be seen from Figure 6(a), as the dielectric constant approaches 0, |S 21 | shows a decreasing trend in the entire frequency band and approaches the limit when the relative dielectric constant reaches 0.2. At this time, |S 21 The maximum value of | is about 8dB lower than that of εr=1. Next, we analyze the effect of magnetic permeability on isolation. r =1, h = 13.34 mm, r = 26.69 mm, in the frequency range of 3.2 GHz - 3.8 GHz | S 21 |With μ r The change of is shown in Figure 6. As can be seen from Figure 6(b), as the permeability approaches 0, |S 21 | also shows a downward trend, but the magnitude of the decrease is smaller than when the dielectric constant is reduced. When the relative permeability reaches 0.2, |S 21 The maximum value of | r = 1, it drops by about 1-2dB. If the dielectric constant and permeability are changed at the same time, and the ideal medium has h = 13.34mm and r = 26.69mm, in the frequency range of 3.2GHz-3.8GHz|S 21 |With ε r and μ r The change of is shown in Figure 6. As can be seen from Figure 6(c), when the dielectric constant and permeability decrease at the same time, |S 21 The maximum value change of | is similar to the effect of changing the dielectric constant only on |S 21|The impact results.

[0040] Next, we analyze the effect of the dielectric thickness h and radius r on the isolation and the effect of dielectric anisotropy on the isolation. Let the ideal dielectric ε r =0.2, μ=1, r=26.69mm, in the frequency range of 3.2GHz-3.8GHz|S 21 | changes with h as shown in Figure 6(d); let ε of the ideal medium be r =0.2, μ=1, h=13.34mm, |S 21 The variation of | with r is shown in Figure 6(e). As can be seen from Figure 6(d), |S 21 |It gradually decreases as h increases, but when h reaches about 25mm|S 21 The decrease of | approaches the limit. From Figure 6(e), it can be seen that |S 21 | also gradually decreases with the increase of r, and as r increases, when r reaches 35mm, |S 21 When analyzing the effect of medium anisotropy on isolation, let μ of the ideal medium be r =1, h = 13.34 mm, r = 26.69 mm. The dielectric constant of the medium is in the five cases shown in Figure 6(f), |S 21 |Changes with frequency in the frequency range of 3.2GHz-3.8GHz. As can be seen from Figure 6(f), reducing the equivalent relative dielectric constant ε in the z direction zz When |S 21 | is significantly smaller than that of the ideal medium without loading, as ε zz decreases rapidly with the decrease of the equivalent relative dielectric constant ε in the x and y directions xx and ε yy When |S 21 |There is little difference from when ideal media is not loaded.

[0041] Furthermore, the effect of negative dielectric constant medium on isolation is analyzed, and μ of ideal medium is set to r =1, h = 20 mm, r = 27 mm, relative dielectric constant ε rThe Lorentz dispersion characteristic is satisfied, the epsilon at infinity is 1.05, the static epsilon is 1.19, the resonant frequency is 3.25 GHz, and the damping frequency is 0.3 GHz. The real and imaginary parts of the dielectric constant of the ideal medium with the Lorentz dispersion parameter vary with frequency in the frequency range of 2.5 GHz to 5 GHz as shown in Figure 7. As can be seen from Figure 7(a), the real part of the relative dielectric constant of the ideal medium is between -1 and 1 at 3.355 GHz to 5 GHz. When this ideal medium is placed between two dipole antennas, in the frequency range of 2.5 GHz to 5 GHz, the |S between the dipole antennas is 21 The variation of | parameter with frequency is shown in Figure 7(b). It can be seen from Figures 7(a) and 7(b) that when the real part of the relative dielectric constant of the ideal medium is between -1 and 1, |S 21 |S in the frequency range of 3.36GHz-3.96GHz is smaller than that without ideal dielectric |S 21 |, and when the dielectric constant is closest to 0, |S 21 The actual bandwidth is smaller than the theoretical bandwidth, which may be affected by factors such as the shape of the medium and simulation errors.

[0042] From the above simulation results, it can be concluded that in the embodiments of the near-zero dielectric constant metamaterial antenna provided in this application, the isolation effect is mainly affected by the equivalent relative dielectric constant ε in the z direction. zz The closer the relative permittivity is to 0 within the range of -1 to 1, the greater the dielectric thickness and radius, and the better the isolation between antennas. Furthermore, near-zero permeability dielectrics can also, to a certain extent, reduce the isolation between electric dipole antennas.

[0043] In each embodiment of the near-zero dielectric constant metamaterial antenna provided in this application, the isolation is mainly increased by the equivalent dielectric constant in the z direction of the medium approaching 0. Therefore, the electric resonance structure formed by the metamaterial unit is used to achieve the near-zero dielectric constant. The most basic electric resonance structure is a metal wire array. In practice, equivalent capacitance and inductance can be introduced by bending metal wires and similar methods, thereby reducing the resonant frequency and reducing the unit size. For the electric resonance unit used in this case, the S parameters of the unit are first calculated, and the equivalent dielectric constant and equivalent magnetic permeability of the unit are obtained by inversion based on the calculated S parameter results. The inversion results are shown in Figure 4. It can be seen that the equivalent relative dielectric constant is between -1 and 1 at the operating frequency of 3.3GHz-3.7GHz, which meets the purpose of the dielectric constant being close to zero as described in this application. It can be understood that in practical applications, the near-zero dielectric constant metamaterial structure has an impact on the isolation effect. Arrange the metamaterial units according to the arrangement method shown in Figure 2, and the metamaterial will have an equivalent relative dielectric constant ε in a certain frequency band in the z direction. zzAccording to the above analysis, the equivalent relative dielectric constant ε in the z direction of the metamaterial is zz When the frequency band satisfies the near-zero characteristic, the |S between the dipole antennas is 21 The calculated S parameter results will be lower than the transmit antenna's |S 21 | Almost unchanged, |S 21 |S is significantly smaller than that without the equivalent near-zero dielectric constant metamaterial in the frequency range of 3.39GHz-3.67GHz. 21 |, which meets the results of the above-mentioned ideal medium equivalent parameter analysis. In fact, the bandwidth when simulating the actual structure of the metamaterial is narrower than the theoretical bandwidth when simulating a single unit, which may be affected by other factors such as inter-unit coupling, the imaginary part of the equivalent dielectric constant and the magnetic permeability. However, compared with other methods such as adding a pec spacer, the method of the case described in the present application has less impact on the input impedance matching and the antenna pattern, so that it can be determined that the target near-zero dielectric constant has a great optimization on the decoupling performance of the near-zero dielectric constant metamaterial antenna. The near-zero dielectric constant metamaterial antenna increases the isolation between the first radiator and the second radiator by arranging a metamaterial structure between the first radiator and the second radiator, thereby reducing the coupling between the first radiator and the second radiator, especially in the near field. In particular, the metamaterial structure includes multiple metamaterial units, each of which is composed of a dielectric unit and a metal wire unit. The metamaterial structure is used to generate electric resonance in a preset direction, thereby reducing the dielectric coefficient of the dielectric unit to near zero, that is, achieving a target near-zero dielectric constant. Simulation of the near-zero dielectric constant metamaterial antenna proves that the target near-zero dielectric constant optimizes the decoupling performance of the near-zero dielectric constant metamaterial antenna.

[0044] It should be understood that the foregoing general description and the following detailed description are exemplary and explanatory only and are not restrictive of the present application.

[0045] Please refer to Figure 8 below, which shows a schematic diagram of an electronic device provided by some embodiments of the present application. As shown in Figure 8, the electronic device 2 includes: a processor 200, a memory 201, a bus 202 and a communication interface 203, and the processor 200, the communication interface 203 and the memory 201 are connected via the bus 202; the memory 201 stores a computer program that can be run on the processor 200, and when the processor 200 runs the computer program, it executes a design method for a near-zero dielectric constant metamaterial antenna as described in any of the embodiments of the present application to verify the isolation or coupling performance of the near-zero dielectric constant metamaterial antenna. The design method includes: obtaining an ideal medium, and simulating a near-zero dielectric constant metamaterial antenna through the ideal medium; determining the degree of optimization of the target near-zero dielectric constant on the decoupling performance of the near-zero dielectric constant metamaterial antenna based on the simulation results.

[0046] The memory 201 may include high-speed random access memory (RAM) and may also include non-volatile memory, such as at least one disk storage. The system network element communicates with at least one other network element via at least one communication interface 203 (which may be wired or wireless), and may utilize the Internet, a wide area network, a local area network, a metropolitan area network, or the like.

[0047] The bus 202 may be an ISA bus, a PCI bus, or an EISA bus. The bus may be divided into an address bus, a data bus, a control bus, etc. The memory 201 is used to store programs. The processor 200 executes the programs upon receiving execution instructions. The design method disclosed in any of the aforementioned embodiments of the present application may be applied to the processor 200 or implemented by the processor 200.

[0048] The processor 200 may be an integrated circuit chip with signal processing capabilities. During implementation, each step of the above method can be completed by hardware integrated logic circuits in the processor 200 or by software instructions. The above processor 200 may be a general-purpose processor, including a central processing unit (CPU), a network processor (NP), etc.; it may also be a digital signal processor (DSP), an application-specific integrated circuit (ASIC), an off-the-shelf field programmable gate array (FPGA), or other programmable logic devices, discrete gate or transistor logic devices, or discrete hardware components. It can implement or execute the various methods, steps, and logic block diagrams disclosed in the embodiments of this application. The general-purpose processor may be a microprocessor or any conventional processor. The steps of the method disclosed in conjunction with the embodiments of this application can be directly implemented and executed by a hardware decoding processor, or by a combination of hardware and software modules in the decoding processor. The software module can be located in a storage medium mature in the art, such as random access memory, flash memory, read-only memory, programmable read-only memory, electrically erasable programmable memory, registers, etc. The storage medium is located in the memory 201, and the processor 200 reads the information in the memory 201 and completes the steps of the design method in combination with its hardware.

[0049] The present application also provides a computer-readable storage medium corresponding to the design method provided in the aforementioned embodiment, on which a computer program is stored. When the computer program is executed by a processor, the design method provided in any of the aforementioned embodiments is executed. In addition, examples of the computer-readable storage medium may include, but are not limited to, phase change memory (PRAM), static random access memory (SRAM), dynamic random access memory (DRAM), other types of random access memory (RAM), read-only memory (ROM), electrically erasable programmable read-only memory (EEPROM), flash memory or other optical or magnetic storage media, which are not listed here one by one.

[0050] In addition, embodiments of the present application further provide a computer program product, including a computer program that, when executed by a processor, implements the steps of the design method for a near-zero dielectric constant metamaterial antenna according to any of the aforementioned embodiments. The steps include: obtaining an ideal medium, simulating a near-zero dielectric constant metamaterial antenna using the ideal medium, and determining, based on the simulation results, the degree to which the target near-zero dielectric constant optimizes the decoupling performance of the near-zero dielectric constant metamaterial antenna.

[0051] Those skilled in the art will appreciate that the various component embodiments of the present application can be implemented in hardware, or in software modules running on one or more processors, or in a combination thereof. Those skilled in the art will appreciate that in practice, a microprocessor or digital signal processor (DSP) can be used to implement some or all of the functions of some or all of the components of the apparatus for creating a virtual machine according to an embodiment of the present application.

[0052] The above description is merely a preferred embodiment of the present application, but the scope of protection of the present application is not limited thereto. Any changes or substitutions that can be easily conceived by a person skilled in the art within the technical scope disclosed in this application should be included in the scope of protection of the present application. Therefore, the scope of protection of the present application should be based on the scope of protection of the claims.

Claims

1. A near-zero dielectric constant metamaterial antenna, characterized in that: The near-zero dielectric constant metamaterial antenna includes a first radiator, a second radiator, and a metamaterial structure; the metamaterial structure is arranged between the first radiator and the second radiator; the metamaterial structure includes a plurality of metamaterial units, each metamaterial unit is composed of a dielectric unit and a metal wire unit, and the metamaterial structure is used to generate electric resonance in a preset direction to achieve a target near-zero dielectric constant in a preset communication frequency band.

2. The near-zero dielectric constant metamaterial antenna according to claim 1, characterized in that: The first radiator includes a first conductor and a first feeding structure connected to the first conductor, the second radiator includes a second conductor and a second feeding structure connected to the second conductor, and both the first radiator and the second radiator are used to send communication data and / or receive communication data.

3. The near-zero dielectric constant metamaterial antenna according to claim 1, characterized in that: The metal wire unit includes one or more groups of metal wires with preset widths; each metamaterial unit is composed of a dielectric unit and a metal wire unit, including: The one or more groups of metal wires with preset widths are mounted on the substrate surface of the dielectric unit.

4. The near-zero dielectric constant metamaterial antenna according to claim 3, characterized in that: The metal wire unit is a group of metal wires mounted on the central area of ​​the substrate surface of the dielectric unit; The metal wire unit is a plurality of groups of metal wires, and there is a preset distance between each group of metal wires.

5. The near-zero dielectric constant metamaterial antenna according to claim 3, characterized in that: Each group of metal wires has a multiple bending structure.

6. The near-zero dielectric constant metamaterial antenna according to claim 5, characterized in that: The multiple bending structure is obtained by bending the metal wire multiple times by 90 degrees on the substrate surface of the dielectric unit.

7. The near-zero dielectric constant metamaterial antenna according to claim 1, characterized in that: A first supporting structure is also connected between the first radiator and the metamaterial structure.

8. The near-zero dielectric constant metamaterial antenna according to claim 1, characterized in that: A second supporting structure is also connected between the metamaterial structure and the second radiator.

9. The near-zero dielectric constant metamaterial antenna according to claim 1, characterized in that: The target near-zero dielectric constant is a real number or a complex number. If the target near-zero dielectric constant is a complex number, the real part of the target near-zero dielectric constant is a real number between -1 and 1.

10. A method for designing a near-zero dielectric constant metamaterial antenna as claimed in any one of claims 1 to 9, characterized in that: The design method comprises: Acquire an ideal medium, and simulate a near-zero dielectric constant metamaterial antenna through the ideal medium; The optimization degree of the target near-zero dielectric constant on the decoupling performance of the near-zero dielectric constant metamaterial antenna is determined according to the simulation results.

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