Communication method and apparatus

Abstract

The present application relates to the technical field of communications, and provides a communication method and apparatus. The method comprises: a sending end acquiring a reference signal sequence and a data signal sequence, and separately mapping the above-described two sequences to time units to obtain a time domain reference signal and a time domain data signal; separately performing transform precoding on the time domain reference signal and the time domain data signal to obtain two groups of frequency domain signals; alternately mapping the two groups of frequency domain signals to P frequency domain units; and performing inverse Fourier transform to obtain a signal to be sent. The time units to which the reference signal sequence is mapped do not overlap with the time units to which the data signal sequence is mapped, and among the time units to which the reference signal sequence and the data signal sequence are mapped, the absolute value of a phase difference between elements mapped on any two adjacent time units is θ (θ≠0). The reference signal sequence has a time domain density of (1 / R), and R is an integer greater than 2. The above-described method may enable the signal to be sent to have a low PAPR.

Description

Communication methods and devices

[0001] This application claims priority to Chinese Patent Application No. 202410911709.0, filed on July 8, 2024, entitled "Communication Method and Apparatus", the entire contents of which are incorporated herein by reference. Technical Field

[0002] This application relates to the field of communication technology, and in particular to communication methods and apparatus. Background Technology

[0003] In a communication system, the data signal sent by the transmitter can be received by the receiver after passing through the transmission channel. The data signal undergoes changes during transmission (e.g., noise is added, or the signal fades), so the data signal received by the receiver differs from the data signal sent by the transmitter. To accurately reconstruct the data signal sent by the transmitter, the receiver needs to understand the changes the data signal underwent during transmission; therefore, a reference signal (RS) is introduced.

[0004] A reference signal is a known signal that can be transmitted along with the data signal in the transmission channel. The receiver compares the received reference signal with the actual reference signal to estimate the changes in the data signal transmitted along with the reference signal in the transmission channel, thus reconstructing the received data signal from the transmitted signal. Furthermore, reference signals can also be used for channel quality measurement, obtaining weights for analog beamforming, or target sensing.

[0005] Typically, reference and data signals are transmitted using time-division multiplexing, meaning they are transmitted through different time-domain resources. This approach results in low spectral efficiency. Therefore, a frequency-division multiplexing scheme has been proposed, where reference and data signals are transmitted through different frequency-domain resources. However, this approach leads to a higher peak-to-average power ratio (PAPR) of the transmitted signal, resulting in lower transmission power and impacting coverage. Summary of the Invention

[0006] This application provides a communication method and apparatus that can reduce the PAPR of the transmitted signal when the reference signal and data signal are transmitted in a frequency division multiplexing manner, thereby increasing the transmission power of the transmitted signal and improving coverage.

[0007] To achieve the above objectives, this application adopts the following technical solution:

[0008] Firstly, a communication method is provided, which can be executed by a transmitting end. Here, "transmitting end" can refer to the transmitting end itself, or to a processor, circuit, module, logic node, chip, or chip system within the transmitting end that implements the method. For example, the transmitting end can be a radio access network (RAN) node or terminal.

[0009] The method includes: acquiring a first reference signal sequence and a first data signal sequence; mapping the first reference signal sequence to time units to obtain a first time-domain reference signal, and mapping the first data signal sequence to time units to obtain a first time-domain data signal; performing transform precoding on the first time-domain reference signal and the first time-domain data signal respectively to obtain two sets of frequency-domain signals; interleaving and mapping the two sets of frequency-domain signals to P frequency-domain units to obtain P frequency-domain signals; performing inverse Fourier transform on the P frequency-domain signals to obtain the signal to be transmitted; and transmitting the signal to be transmitted. The time units mapping the first reference signal sequence and the time units mapping the first data signal sequence do not overlap. In the time units mapping the first reference signal sequence and the first data signal sequence, the absolute value of the phase difference between the mapped elements in any two adjacent time units is θ. The time-domain density of the first reference signal sequence is (1 / R), which is used to determine the number of time units mapping the first reference signal sequence. R is an integer greater than 2, and θ is not equal to 0. P is greater than or equal to twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0010] Based on the method provided in the first aspect above, the transmitting end can map the first data signal sequence and the first reference signal sequence to non-overlapping time and frequency domain positions, and perform transform-domain precoding, thereby enabling the signal to be transmitted to possess single-carrier characteristics. Furthermore, in the time units of mapping the first data signal sequence and the first reference signal sequence, the absolute value of the phase difference between the mapped elements in any two adjacent time units is θ, which can reduce the envelope fluctuation of the signal to be transmitted. Therefore, the method provided in the first aspect above can enable the signal to be transmitted to have a low PAPR. Utilizing this characteristic, after increasing the power of the signal to be transmitted, the signal is less prone to distortion, thereby improving coverage.

[0011] In one possible implementation, θ is π / 2.

[0012] In one possible implementation, acquiring the first data signal sequence includes: acquiring... Binary phase shift keying sequence; for The elements in the binary phase shift keying sequence are transposed and / or phase rotated to obtain the first data signal sequence.

[0013] Based on the above possible implementation methods, the following can be adopted: Binary phase shift keying modulates the data bit sequence to obtain the first data signal sequence.

[0014] In one possible implementation, obtaining the first data signal sequence includes: obtaining multiple binary phase shift keying sequences; and obtaining the first data signal sequence based on the multiple binary phase shift keying sequences.

[0015] Based on the above possible implementation methods, binary phase shift keying (BPSK) modulation of the data bit sequence can be used to obtain the first data signal sequence. It should be understood that at least two of the multiple binary BPSK sequences correspond to different modulation schemes. Taking two binary BPSK sequences as an example, one binary BPSK sequence can contain all real numbers, while the other binary BPSK sequence can contain all imaginary numbers.

[0016] In one possible implementation, transform-domain precoding is performed on the first time-domain reference signal and the first time-domain data signal respectively to obtain two sets of frequency-domain signals. This includes: performing phase rotation on the elements in the first time-domain reference signal to obtain a second time-domain reference signal, and performing transform-domain precoding on the second time-domain reference signal and the first time-domain data signal respectively to obtain two sets of frequency-domain signals; or, performing phase rotation on the elements in the first time-domain data signal to obtain a second time-domain data signal, and performing transform-domain precoding on the first time-domain reference signal and the second time-domain data signal respectively to obtain two sets of frequency-domain signals.

[0017] Based on the above possible implementation methods, the elements in the first time-domain reference signal or the elements in the first time-domain data signal can be phase-rotated, so that after the two sets of frequency domain signals are interleaved and mapped, the absolute value of the phase difference between the elements mapped in any two adjacent time units in the time units of the first data signal sequence and the first reference signal sequence is still θ.

[0018] In one possible implementation, interleaving and mapping two sets of frequency domain signals to P frequency domain units includes: mapping one set of frequency domain signals to the 2p-th frequency domain unit among the P frequency domain units; mapping the other set of frequency domain signals to the (2p+1)-th frequency domain unit among the P frequency domain units; where p is greater than or equal to 0 and less than 1. Integers, where This indicates rounding down to the nearest integer.

[0019] Based on the above possible implementation methods, the data signal can be evenly distributed across P frequency domain units to maximize the acquisition of channel frequency selectivity gain.

[0020] In one possible implementation, P is equal to twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0021] In one possible implementation, P is greater than twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0022] In one possible implementation, performing an inverse Fourier transform on P frequency domain signals to obtain the signal to be transmitted includes: performing spectrum shaping processing on the P frequency domain signals, and performing an inverse Fourier transform on the spectrum-shaped signals to obtain the signal to be transmitted.

[0023] Based on the above possible implementation methods, PAPR can be reduced. Understandably, when P is greater than twice the sum of the lengths of the first reference signal sequence and the first data signal sequence, the effect of reducing PAPR is even better.

[0024] In one possible implementation, R equals 3, 4, or 5.

[0025] Based on the above possible implementations, when R equals 3, in the first time domain reference signal, one time unit out of every three time units carries an element of the first reference signal sequence; when R equals 4, in the first time domain reference signal, one time unit out of every four time units carries an element of the first reference signal sequence; when R equals 5, in the first time domain reference signal, one time unit out of every five time units carries an element of the first reference signal sequence.

[0026] In one possible implementation, when R equals 3 or 5, the first reference signal sequence is: Binary phase shift keying sequence; when R equals 4, the first reference signal sequence is a binary phase shift keying sequence.

[0027] Based on the above possible implementations, when R equals 3 or 5, the sending end can adopt... The first reference signal sequence is obtained by using a preset bit sequence of binary phase shift keying modulation. When R equals 4, the transmitter can use the preset bit sequence of binary phase shift keying modulation to obtain the first reference signal sequence.

[0028] In one possible implementation, the ratio of the energy per resource unit corresponding to the first data signal sequence to the energy per resource unit corresponding to the first reference signal sequence is related to R.

[0029] Based on the above possible implementation methods, the sending end can determine the ratio based on R without interacting with the receiving end to obtain the ratio, thus reducing signaling overhead.

[0030] In one possible implementation, any two elements in the first reference signal sequence have the same modulus, and any two elements in the first data signal sequence have the same modulus.

[0031] Based on the above possible implementation methods, the PAPR of the signal to be transmitted can be reduced.

[0032] In one possible implementation, the modulus of an element in the first reference signal sequence is the same as the modulus of an element in the first data signal sequence.

[0033] Based on the above possible implementation methods, the PAPR of the signal to be transmitted can be reduced.

[0034] Secondly, a communication method is provided, which can be executed by a receiving end. Here, the receiving end can refer to the receiving end itself, or to a processor, circuit, module, logic node, chip, or chip system within the receiving end that implements the method. For example, the receiving end can be a RAN node or a terminal.

[0035] The method includes: receiving a signal transmitted by a transmitter; performing transform-domain precoding on the received signal to obtain two sets of frequency domain signals, one set of frequency domain signals including the frequency domain signal corresponding to a first data signal sequence, and the other set of frequency domain signals including the frequency domain signal corresponding to a first reference signal sequence; the two sets of frequency domain signals are interleaved and mapped in the frequency domain; in the time domain, the time units mapping the first data signal sequence and the time units mapping the first reference signal sequence do not overlap; in the time units mapping the first data signal sequence and the first reference signal sequence, the absolute value of the phase difference between any two adjacent time units mapped is θ; the time domain density of the first reference signal sequence is (1 / R), and the time domain density of the first reference signal sequence is used to determine the number of time units mapping the first reference signal sequence, where R is an integer greater than 2 and θ is not equal to 0; performing channel equalization on the frequency domain signal corresponding to the first data signal sequence; performing an inverse Fourier transform on the channel-equalized signal to obtain a first time domain data signal, in which the absolute value of the phase difference between any two adjacent elements is θ or 0; and obtaining a first data signal sequence based on the first time domain data signal.

[0036] Based on the method provided in the second aspect above, the receiving end can perform operations such as transform-domain precoding, channel equalization, and inverse Fourier transform on the received signal to obtain a first data signal sequence. The first data signal sequence and the first reference signal sequence can be mapped to different time-domain and frequency-domain positions, and within the time units of mapping the first data signal sequence and the first reference signal sequence, the absolute value of the phase difference between the mapped elements in any two adjacent time units is θ. This can reduce the fluctuation of the envelope of the signal to be transmitted. Therefore, the method provided in the second aspect above can enable the signal transmitted by the transmitting end to have a low PAPR. Utilizing this characteristic, after increasing the power of the signal transmitted by the transmitting end, the signal is less prone to distortion, thereby improving coverage.

[0037] In one possible implementation, θ is π / 2.

[0038] In one possible implementation, the two sets of frequency domain signals are interleaved and mapped in the frequency domain, including: one set of frequency domain signals is mapped to the 2p-th frequency domain unit out of P frequency domain units, and the other set of frequency domain signals is mapped to the (2p+1)-th frequency domain unit out of P frequency domain units; where p is greater than or equal to 0 and less than 1. Integers, where This indicates rounding down to the nearest integer.

[0039] Based on the above possible implementation methods, the data signal can be evenly distributed across P frequency domain units to maximize the acquisition of channel frequency selectivity gain.

[0040] In one possible implementation, P is equal to twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0041] In one possible implementation, P is greater than twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0042] In one possible implementation, R equals 3, 4, or 5.

[0043] Based on the above possible implementations, when R equals 3, in the first time domain reference signal, one time unit out of every three time units carries an element from the first reference signal sequence; when R equals 4, in the first time domain data signal, one time unit out of every four time units carries an element from the first reference signal sequence; and when R equals 5, in the first time domain data signal, one time unit out of every five time units carries an element from the first reference signal sequence.

[0044] In one possible implementation, when R equals 3 or 5, the first reference signal sequence is: Binary phase shift keying sequence; when R equals 4, the first reference signal sequence is a binary phase shift keying sequence.

[0045] In one possible implementation, the ratio of the energy per resource unit corresponding to the first data signal sequence to the energy per resource unit corresponding to the first reference signal sequence is related to R.

[0046] Based on the above possible implementation methods, the receiving end can determine the ratio based on R without interacting with the sending end to obtain the ratio, thus reducing signaling overhead.

[0047] In one possible implementation, any two elements in the first reference signal sequence have the same modulus, and any two elements in the first data signal sequence have the same modulus.

[0048] Based on the above possible implementation methods, the PAPR of the signal transmitted by the transmitter can be reduced.

[0049] In one possible implementation, the modulus of an element in the first reference signal sequence is the same as the modulus of an element in the first data signal sequence.

[0050] Based on the above possible implementation methods, the PAPR of the signal transmitted by the transmitter can be reduced.

[0051] Thirdly, a communication device is provided for implementing the method provided in the first aspect. This communication device can be the transmitting end in the first aspect. The communication device includes modules, units, or means corresponding to the above method, which can be implemented in hardware, software, or by hardware executing corresponding software. The hardware or software includes one or more modules or units corresponding to the above functions.

[0052] In one possible implementation, the communication device may include a processing module and an interface module. The processing module can be used to implement the processing functions described in the first aspect and any possible implementation thereof. The processing module may be, for example, a processor. The interface module, also referred to as an interface unit, is used to implement the sending and / or receiving functions described in the first aspect and any possible implementation thereof. The interface module may consist of an interface circuit, a transceiver, a transceiver unit, or a communication interface.

[0053] In one possible implementation, the processing module is configured to acquire a first reference signal sequence and a first data signal sequence. The processing module is further configured to map the first reference signal sequence and the first data signal sequence to time units respectively, obtaining a first time-domain reference signal and a first time-domain data signal. The time units mapping the first reference signal sequence and the time units mapping the first data signal sequence do not overlap. In the time units mapping the first reference signal sequence and the first data signal sequence, the absolute value of the phase difference between the mapped elements in any two adjacent time units is θ. The time-domain density of the first reference signal sequence is (1 / R), and the time-domain density of the first reference signal sequence is used to determine the number of time units mapping the first reference signal sequence. R is an integer greater than 2, and θ is not equal to 0. The processing module is further configured to perform transform-domain precoding on the first time-domain reference signal and the first time-domain data signal respectively to obtain two sets of frequency-domain signals; the processing module is further configured to interleave and map the two sets of frequency-domain signals to P frequency-domain units to obtain P frequency-domain signals, where P is greater than or equal to twice the sum of the lengths of the first reference signal sequence and the first data signal sequence; the processing module is further configured to perform inverse Fourier transform on the P frequency-domain signals to obtain the signal to be transmitted; the interface module is configured to transmit the signal to be transmitted.

[0054] In one possible implementation, θ is π / 2.

[0055] In one possible implementation, the processing module is specifically used to obtain Binary phase-shift keying sequence; this processing module is also specifically used for this The elements in the binary phase shift keying sequence are transposed and / or phase rotated to obtain the first data signal sequence.

[0056] In one possible implementation, the processing module is specifically used to acquire multiple binary phase shift keying (PSK) sequences; the processing module is also specifically used to obtain the first data signal sequence based on the multiple binary PSK sequences. It is understood that at least two of the multiple binary PSK sequences correspond to different modulation schemes. Taking two binary PSK sequences as an example, the elements in one binary PSK sequence can all be real numbers, and the elements in the other binary PSK sequence can all be imaginary numbers.

[0057] In one possible implementation, the processing module is specifically used to perform phase rotation on the elements in the first time-domain reference signal to obtain a second time-domain reference signal, and to perform transform-domain precoding on the second time-domain reference signal and the first time-domain data signal respectively to obtain the two sets of frequency-domain signals; or, the processing module is specifically used to perform phase rotation on the elements in the first time-domain data signal to obtain a second time-domain data signal, and to perform transform-domain precoding on the first time-domain reference signal and the second time-domain data signal respectively to obtain the two sets of frequency-domain signals.

[0058] In one possible implementation, the processing module is specifically configured to map one of the two sets of frequency domain signals to the 2p-th frequency domain unit among the P frequency domain units; the processing module is also specifically configured to map the other set of frequency domain signals to the (2p+1)-th frequency domain unit among the P frequency domain units; where p is greater than or equal to 0 and less than 1. Integers, where This indicates rounding down to the nearest integer.

[0059] In one possible implementation, P is equal to twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0060] In one possible implementation, P is greater than twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0061] In one possible implementation, the processing module is specifically used to perform spectrum shaping on P frequency domain signals, and to perform inverse Fourier transform on the spectrum-shaped signals to obtain the signal to be transmitted.

[0062] In one possible implementation, R is equal to 3, 4, or 5.

[0063] In one possible implementation, when R equals 3 or 5, the first reference signal sequence is: Binary phase shift keying sequence; when R equals 4, the first reference signal sequence is a binary phase shift keying sequence.

[0064] In one possible implementation, the ratio of the energy per resource unit corresponding to the first data signal sequence to the energy per resource unit corresponding to the first reference signal sequence is related to R.

[0065] In one possible implementation, any two elements in the first reference signal sequence have the same modulus, and any two elements in the first data signal sequence have the same modulus.

[0066] In one possible implementation, the modulus of the elements in the first reference signal sequence is the same as the modulus of the elements in the first data signal sequence.

[0067] Fourthly, a communication device is provided for implementing the method provided in the second aspect. This communication device can be the receiving end described in the second aspect. The communication device includes modules, units, or means that implement the method described above. These modules, units, or means can be implemented in hardware, software, or by hardware executing corresponding software. The hardware or software includes one or more modules or units corresponding to the functions described above.

[0068] In one possible implementation, the communication device may include a processing module and an interface module. The processing module can be used to implement the processing functions in the second aspect described above and any possible implementation thereof. The processing module may be, for example, a processor. The interface module, also referred to as an interface unit, is used to implement the sending and / or receiving functions in the second aspect described above and any possible implementation thereof. The interface module may consist of an interface circuit, a transceiver, a transceiver unit, or a communication interface.

[0069] In one possible implementation, the interface module is used to receive signals transmitted by the transmitter; the processing module is used to perform transform-domain precoding on the received signals to obtain two sets of frequency-domain signals, one set of frequency-domain signals including the frequency-domain signal corresponding to the first data signal sequence, and the other set of frequency-domain signals including the frequency-domain signal corresponding to the first reference signal sequence. These two sets of frequency-domain signals are interleaved and mapped in the frequency domain. In the time domain, the time units mapping the first data signal sequence and mapping the first reference signal sequence do not overlap. Within the time units mapping the first data signal sequence and the first reference signal sequence, the phase difference between the mapped elements in any two adjacent time units is... The absolute value of the difference is θ. The time-domain density of the first reference signal sequence is (1 / R). The time-domain density of the first reference signal sequence is used to determine the number of time units mapping the first reference signal sequence. R is an integer greater than 2, and θ is not equal to 0. The processing module is also used to perform channel equalization on the frequency domain signal corresponding to the first data signal sequence. The processing module is also used to perform inverse Fourier transform on the channel-equalized signal to obtain the first time-domain data signal. In the first time-domain data signal, the absolute value of the phase difference between any two adjacent elements is θ or 0. The processing module is also used to obtain the first data signal sequence based on the first time-domain data signal.

[0070] In one possible implementation, θ is π / 2.

[0071] In one possible implementation, the two sets of frequency domain signals are interleaved and mapped in the frequency domain, including: one set of frequency domain signals is mapped to the 2p-th frequency domain unit out of P frequency domain units, and the other set of frequency domain signals is mapped to the (2p+1)-th frequency domain unit out of P frequency domain units; where p is greater than or equal to 0 and less than 1. Integers, where This indicates rounding down to the nearest integer.

[0072] In one possible implementation, P is equal to twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0073] In one possible implementation, P is greater than twice the sum of the lengths of the first reference signal sequence and the first data signal sequence.

[0074] In one possible implementation, R is equal to 3, 4, or 5.

[0075] In one possible implementation, when R equals 3 or 5, the first reference signal sequence is: Binary phase shift keying sequence; when R equals 4, the first reference signal sequence is a binary phase shift keying sequence.

[0076] In one possible implementation, the ratio of the energy per resource unit corresponding to the first data signal sequence to the energy per resource unit corresponding to the first reference signal sequence is related to R.

[0077] In one possible implementation, any two elements in the first reference signal sequence have the same modulus, and any two elements in the first data signal sequence have the same modulus.

[0078] In one possible implementation, the modulus of the elements in the first reference signal sequence is the same as the modulus of the elements in the first data signal sequence.

[0079] Fifthly, a communication device is provided, comprising: a processor; configured to cause the communication device to perform the method described in any of the preceding aspects by executing a computer program (or computer-executable instructions) stored in a memory, and / or by means of logic circuitry. The communication device may be a transmitting end as described in the first aspect; or, the communication device may be a receiving end as described in the second aspect. Optionally, the number of processors may be one or more.

[0080] In one possible implementation, the communication device further includes a memory, or the memory may be located outside the communication device.

[0081] In one possible implementation, the processor and memory are integrated together; alternatively, the memory is independent of the processor.

[0082] In one possible implementation, the communication device further includes a communication interface for communicating with other devices, such as transmitting or receiving data and / or signals. Exemplarily, the communication interface may be a transceiver, circuit, bus, module, or other type of communication interface.

[0083] In one possible implementation, the processor and / or memory also include an artificial intelligence (AI) module for implementing AI-related functions. The AI ​​module can implement AI functions through software, hardware, or a combination of both. For example, the AI ​​module may include a radio access network (RAN) intelligent controller (RIC) module. The AI ​​module could be a near real-time RIC or a non-real-time RIC.

[0084] In one possible implementation, the communication device is a chip or a chip system. Optionally, when the communication device is a chip system, it can be composed of chips or may include chips and other discrete components.

[0085] A sixth aspect provides a communication device, comprising: a processor and an interface circuit; the interface circuit being configured to receive a computer program or instructions and transmit them to the processor; the processor being configured to execute the computer program or instructions to cause the communication device to perform the method described in any of the preceding aspects. The communication device may be a transmitting end as described in the first aspect; or, the communication device may be a receiving end as described in the second aspect. Optionally, the number of processors may be one or more.

[0086] In one possible implementation, the processor also includes an AI module for implementing AI-related functions. The AI ​​module can implement AI functions through software, hardware, or a combination of both. For example, the AI ​​module may include a RIC module. The AI ​​module could be a near real-time RIC or a non-real-time RIC.

[0087] In one possible implementation, the communication device is a chip or a chip system. Optionally, when the communication device is a chip system, it can be composed of chips or may include chips and other discrete components.

[0088] In a seventh aspect, a computer-readable storage medium is provided, which stores instructions that, when executed on a computer, cause the computer to perform the methods described in any of the preceding aspects.

[0089] Eighthly, a computer program product containing instructions is provided, which, when run on a computer, enables the computer to perform the methods described in any of the preceding aspects.

[0090] A ninth aspect provides a communication system comprising a transmitting end for performing the method described in the first aspect and a receiving end for performing the method described in the second aspect.

[0091] The technical effects of any possible implementation of aspects three through nine can be found in the technical effects of any one of aspects one through two or different possible implementations of any one of aspects, and will not be repeated here.

[0092] Understandably, provided that the solutions do not contradict each other, the solutions in the above aspects can be combined. Attached Figure Description

[0093] Figure 1A is a schematic diagram of the architecture of an orthogonal frequency division multiplexing (OFDM) system;

[0094] Figure 1B is a schematic diagram of the architecture of a Discrete Fourier Transform Spread Orthogonal Frequency Division Multiplexing (DFT-s-OFDM) system.

[0095] Figure 1C is A schematic diagram of the trajectory of a binary phase shift keying (BPSK) symbol sequence;

[0096] Figure 1D is a schematic diagram of the input / output power curves of the power amplifier;

[0097] Figure 1E is a schematic diagram of Type 1 dual-symbol demodulation reference signal (DMRS);

[0098] Figure 1F is a schematic diagram of double-symbol DMRS Type 2;

[0099] Figure 1G is a schematic diagram of the data and resources occupied by DMRS within a resource block (RB);

[0100] Figure 1H is a schematic diagram of the data within one RB and the resources occupied by DMRS (second diagram).

[0101] Figure 1I is a schematic diagram of frequency division multiplexing of data signal and reference signal provided in this application;

[0102] Figure 1J is a schematic diagram of frequency division multiplexing of data signals and reference signals provided in this application;

[0103] Figure 1K is a schematic diagram of the PAPR relationship of the transmitted signal provided in this application;

[0104] Figure 2 is a schematic diagram of the communication system architecture provided in this application;

[0105] Figure 3 is a schematic diagram of the hardware structure of the communication device provided in this application;

[0106] Figure 4 is a flowchart illustrating the communication method provided in this application;

[0107] Figure 5A is a schematic diagram of the time-domain density of the first reference signal sequence provided in this application;

[0108] Figure 5B is a schematic diagram of the frequency domain density of the first reference signal sequence provided in this application;

[0109] Figure 6A is a schematic diagram of the sending end processing flow provided in this application;

[0110] Figure 6B is a schematic diagram of the sending end processing flow provided in this application (II).

[0111] Figure 6C is a schematic diagram of the sending end processing flow provided in this application;

[0112] Figure 6D is a schematic diagram of the sending end processing flow provided in this application;

[0113] Figure 7 is a schematic diagram of the communication device provided in this application. Detailed Implementation

[0114] Before introducing the technical solution of this application, the relevant technical terms involved in this application are explained. It is understood that these explanations are intended to make this application easier to understand and should not be regarded as a limitation on the scope of protection claimed in this application.

[0115] 1. OFDM

[0116] OFDM is a multi-carrier modulation (MCM) technique. Its core principle is to divide the channel into several orthogonal sub-channels and perform narrowband modulation and transmission on each sub-channel to reduce interference between them. Figure 1A illustrates an example of an OFDM system architecture. In Figure 1A, the data sequence at the transmitting end undergoes sequential processing including serial-to-parallel (S / P), subcarrier mapping, N-point inverse discrete fourier transform (IDFT), parallel-to-serial (P / S), cyclic prefix (CP), and digital-to-analog converter (DAC) before being transmitted as a radio frequency (RF) signal. This signal then reaches the receiving end after transmission through the channel. Accordingly, the signal received by the receiver can be processed sequentially through analog-to-digital converter (ADC), cyclic prefix removal, serial-to-parallel conversion, N-point discrete Fourier transform (DFT), subcarrier demapping / equalization, and parallel-to-serial conversion to obtain the above data sequence.

[0117] Taking a data sequence of S(kM), S(kM+1), ..., S(kM+M-1) as an example, serial-to-parallel conversion can convert the data sequence into an M-dimensional data block, such as S k =[S(kM),S(kM+1),…,S(kM+M-1)] T Where k is the OFDM symbol number, [] T This indicates transpose. S can be achieved through subcarrier mapping. k The M data carried modulate N subcarriers. sc N subcarriers, of which N sc =M, the rest (NN) sc The subcarriers can be understood as being modulated by data 0. After subcarrier mapping, an N-dimensional data vector X can be obtained. k X k After N-point IDFT and parallel-to-serial conversion, a set of N complex time-domain sampling points x can be obtained. k (0),x k (1),…,x k (N-1). These N complex time-domain sampling points xk (n) can satisfy the following relationship: Where n = 0, 1, ..., N-1, n′ = 0, 1, ..., N-1, X k (n′) represents the output of the subcarrier mapping, e represents Euler's constant, and j represents the imaginary unit. 2 =-1. Subcarrier mapping input S k and output X k (n′) can satisfy the following relationship:

[0118] Where n0 is an integer, S k (l) is S k The l-th element, l = 0, 1, ..., N sc -1, elsewhere means except for n′∈{n0,n0+1,…,n0+M} sc Cases other than -1}.

[0119] After parallel-to-serial conversion, the transmitter can insert a guard field at the beginning of each OFDM symbol, such as adding a CP at the beginning of the OFDM symbol, to eliminate inter-symbol interference (ISI) caused by multipath propagation (such as radio signals reaching the receiver through two or more paths). Let the OFDM symbol be x. k Taking (n) as an example, the sender can copy x. k The last G sampling points of (n) are appended to x. k At the beginning of (n), the time-domain OFDM signal is obtained. That is, an OFDM symbol contains valid data x k (n) and CP, where CP can be considered as redundant data.

[0120] Correspondingly, after receiving the OFDM signal, the receiver can demodulate it through inverse processing. For example, if time and frequency synchronization can be obtained and the cyclic prefix length is sufficient, the receiver can perform a cyclic prefix removal operation (e.g., removing the first G samples from the received signal) to obtain a data block containing N samples with no ISI. This data block can be equivalent to the OFDM symbol x. k The time-domain circular convolution is then performed with the channel impulse response. Subsequently, the receiver can convert the time-domain circular convolution into a frequency-domain dot product using DFT, and then perform channel equalization with low complexity using frequency-domain single-tap equalization.

[0121] As is understandable, the above data sequence is a sequence obtained by modulating a data signal, so S kThis can include modulation symbols and / or redundant signal sampling points. Modulation symbols, also known as modulation signals, can be obtained by modulating a (coded) bitstream. Redundant signal sampling points can include phase tracking reference signal (PTRS) sampling points, demodulation reference signals, tone-preserving signals, etc.

[0122] Understandable, if N sc N represents the number of subcarriers within the transmission bandwidth. sc It can be equal to M, N sc It can also be greater than M. For example, in this application, S of length M can be... k Perform sequence expansion, assuming the length of the expanded sequence is equal to N. sc .

[0123] 2. DFT-s-OFDM

[0124] DFT-s-OFDM, also known as single-carrier OFDM or linear precoding OFDM, is a single-carrier technology based on OFDM waveforms. It can also be understood as a modulation method that uses multiple carriers to achieve a single-carrier waveform. The difference between DFT-s-OFDM and OFDM is that the transmitter can perform a DFT before subcarrier mapping, giving the DFT-s-OFDM signal single-carrier characteristics. Correspondingly, the receiver can perform an IDFT after decarrier mapping. Figure 1B illustrates the architecture of a DFT-s-OFDM system. In Figure 1B, the data sequence at the transmitter undergoes serial-to-parallel conversion, M-point DFT, subcarrier mapping, N-point IDFT, parallel-to-serial conversion, cyclic prefix addition, and digital-to-analog conversion before being transmitted as a radio frequency signal. This signal then reaches the receiver after transmission through the channel. Accordingly, the signal received at the receiving end can be sequentially processed through analog-to-digital conversion, cyclic prefix removal, serial-to-parallel conversion, N-point DFT, subcarrier demapping, M-point IDFT, and parallel-to-serial conversion to obtain the aforementioned data sequence. Specifically, the M-dimensional data block S obtained at the transmitting end after serial-to-parallel conversion and M-point DFT... k This may include modulation symbols and / or redundant signal sampling points. Modulation symbols can be obtained by modulating the (encoded) bitstream. Redundant signal sampling points may include PTRS sampling points, unique words, zeros, etc.

[0125] 3. Modulation method

[0126] The data sequences in Figures 1A and 1B above are obtained through modulation. In practical applications, there are various modulation methods, such as pulse amplitude modulation (PAM), frequency shift keying (FSK), phase shift keying (PSK), and BPSK. Quadrature phase shift keying (QPSK), quadrature amplitude modulation (QAM), amplitude phase shift keying (APSK), and offset quadrature amplitude modulation (OQAM) are some of the techniques used. QPSK can also be referred to as 4QAM.

[0127] For example, taking a BPSK modulation mapper as an example, this mapper can map 1 bit in a bitstream to 1 BPSK symbol. For instance, the i-th bit b(i) in the bitstream can be mapped to the i-th BPSK symbol d(i) according to the following relationship:

[0128] For example, with Taking a modulation mapper as an example, this mapper can map 1 bit in a bitstream to 1... Symbols. For example, the i-th bit b(i) in a bitstream can be mapped to the i-th bit according to the following relationship. Symbol d(i): As can be seen from the above mapping relationship, two adjacent symbols in a symbol sequence The symbol exhibits a 90-degree phase transition. For example, Figure 1C illustrates this. A trajectory diagram of the symbol sequence. In the diagram, the horizontal axis represents... The real part of the symbol, the vertical axis is The imaginary part of the symbol, the phase difference between two adjacent symbols in the sequence is It should be understood that The modulation can be viewed as a type of offset QPSK modulation.

[0129] For example, a QPSK modulation mapper can map two consecutive bits in a bitstream to one QPSK symbol. For instance, the 2i-th bit b(2i) and the (2i+1)-th bit b(2i+1) in the bitstream can be mapped to the i-th QPSK symbol d(i) according to the following relationship:

[0130] For example, taking a 16QAM modulation mapper as an example, this mapper can map four consecutive bits in a bitstream to one 16QAM symbol. For instance, the 4i-th bit b(4i), the (4i+1)-th bit b(4i+1), the (4i+2)-th bit b(4i+2), and the (4i+3)-th bit b(4i+3) in the bitstream can be mapped to the i-th 16QAM symbol d(i) according to the following relationship:

[0131] It should be understood that the above are only some examples of mapping bits in a bitstream to symbols. In specific applications, other mapping relationships / implementations / methods may exist. Taking BPSK modulation as an example, the i-th bit b(i) in the bitstream can also be mapped to the i-th BPSK symbol d(i) according to the following relationship: Where ε is a constant.

[0132] 4. Nonlinear characteristics of power amplifiers (PA)

[0133] Before being transmitted through an antenna, a signal is amplified by a power amplifier. The behavior of a power amplifier is typically described by its amplitude modulation-amplitude modulation (AM-AM) characteristics. For example, Figure 1D shows the AM-AM curve of a power amplifier, which describes the functional relationship between the amplifier's output power and its input power. In the linear region, the output power of the power amplifier increases linearly with the input power; that is, the gain of the power amplifier (e.g., the ratio of the output power to the input power) remains constant, or the slope of the AM-AM curve remains constant. As the input power continues to increase, the power amplifier enters the nonlinear region. The output power no longer increases linearly with the input power, the gain of the power amplifier is compressed, and the slope of the AM-AM curve decreases. When the saturation output power is reached, the output power of the power amplifier no longer increases with the input power, and the slope of the AM-AM curve becomes 0. Therefore, in the nonlinear region, the power amplifier exhibits nonlinear characteristics.

[0134] The nonlinear characteristics of power amplifiers lead to both in-band and out-of-band distortion in the transmitted signal. In-band distortion primarily manifests as amplitude and phase distortion, degrading demodulation / detection performance. Out-of-band distortion mainly manifests as spectral spread / regeneration, increasing interference to users in adjacent channels. Therefore, to mitigate the effects of power amplifier nonlinearity, the input signal power can be appropriately reduced, such as through input backoff (IBO) or output backoff (OBO), to keep the power amplifier operating within its linear region. This approach comes at the cost of reduced power amplifier efficiency.

[0135] 5. PAPR

[0136] PAPR refers to the ratio of the peak power to the mean power of a signal over a certain period of time. The unit of PAPR can be dB. For example, if the peak power of signal x(t) is 10 ... The mean power of signal x(t) is The PAPR of this signal satisfies the following relationship:

[0137] Understandably, communication signals (such as OFDM signals or DFT-s-OFDM signals) are random signals. Their mean power can be considered a fixed value, while their peak power is a random variable. Therefore, the PAPR of a communication signal is also a random variable. In statistics, the value of a random signal at a certain moment is often described by a probability density function. Therefore, in the communications industry, engineers often use the complementary cumulative distribution function (CCDF) curve to describe PAPR. For example, the probability that the instantaneous power exceeds the mean power by xx dB is yy, or the proportion of time when the instantaneous power exceeds the mean power by xx dB is yy. Specifically, this can be described by the following relationship:

[0138] Where P(·) represents probability.

[0139] Understandably, a higher PAPR (Power Amplifier Back-Up Rate) for the input signal of a power amplifier means a wider range of input power fluctuation. Therefore, to ensure the entire input / output signal remains within the linear region, more power back-up is required. Thus, designing a signal with low PAPR can reduce the input / output power back-up of the power amplifier, increase signal transmission power, and improve signal coverage.

[0140] Single-carrier signals have a significantly lower PAPR than multi-carrier signals. For example, the PAPR of a DFT-s-OFDM signal, which possesses single-carrier characteristics, is much lower than that of an OFDM signal. With the same power amplifier, a DFT-s-OFDM signal can provide greater output power and higher power amplifier efficiency, thereby improving coverage and reducing energy consumption.

[0141] 6. Port

[0142] A port, also known as an antenna port, is a logical concept referring to a logical port used for transmission to distinguish multiple signals occupying the same time-frequency resources but different spatial resources. There is a mapping relationship between ports and physical antennas; for example, a port can be a single physical antenna or a weighted combination of multiple physical antennas. Typically, the mapping relationship between a port and physical antennas is fixed and does not change over time. Therefore, signals transmitted through the same antenna port experience the same or correlated channel conditions.

[0143] 7. Reference Signal

[0144] A reference signal, also known as a pilot signal, is a known signal that can be provided by the transmitter to the receiver. Reference signals can be used for channel estimation, channel sounding, or target sensing. Based on the transmission direction, reference signals can be divided into uplink reference signals and downlink reference signals.

[0145] Uplink reference signals refer to signals sent from the terminal to the RAN node. Examples include DMRS (Directional Modulation and Recognition Signal) or sounding reference signals (SRS). Uplink reference signals can be used for uplink channel estimation (e.g., for coherent demodulation and detection in the RAN node or for precoding calculation), uplink channel quality measurement, or target sensing. Downlink reference signals refer to signals sent from the RAN node to the terminal. Examples include channel state information reference signals (CSI-RS) or tracking reference signals (TRS). Downlink reference signals can be used for downlink channel estimation, downlink channel measurement, or target sensing.

[0146] It is understood that the reference signal mentioned in the following embodiments of this application can be any of the above-mentioned reference signals, that is, the method provided by this application can be applied to any of the above-mentioned reference signals. In order to better understand the method provided by this application, the following embodiments of this application will be described using DMRS as an example. The relevant concepts of DMRS will be briefly described below.

[0147] DMRS can be used to estimate equivalent channels. For example, DMRS can be used to estimate the equivalent channel of the physical uplink shared channel (PUSCH) for coherent demodulation of uplink data. To ensure the quality of channel estimation, different DMRS ports are typically orthogonal. The DMRS corresponding to different DMRS ports are orthogonal in the frequency domain, time-frequency domain, or code domain.

[0148] In the time domain, DMRS can occupy one or two symbols, so DMRS can be divided into single-symbol DMRS and dual-symbol DMRS. In the frequency domain, based on the maximum number of supported antenna ports, DMRS can be divided into Type 1 and Type 2. For Type 1, DMRS is distributed in a comb pattern in the frequency domain, and the DMRS ports can be divided into two code division multiplexing (CDM) groups, with CDM multiplexing used between ports within each group. For example, a single-symbol DMRS supports a maximum of 4 antenna ports, divided into two CDM groups: {1000, 1001} and {1002, 1003}; a dual-symbol DMRS supports a maximum of 8 antenna ports, divided into two CDM groups: {1000, 1001, 1004, 1005} and {1002, 1003, 1006, 1007}.

[0149] For example, Figure 1E illustrates the time-frequency resources occupied by dual-symbol DMRS Type 1. In the time direction, under the regular cyclic prefix, one slot contains 14 symbols (e.g., symbols 0 to 13). In the frequency direction, one RB contains 12 subcarriers (e.g., subcarriers 0 to 11). One resource element (RE) corresponds to one symbol in the time direction and one subcarrier in the frequency direction. In Figure 1E, one antenna port has 6 REs within one RB for transmitting DMRS. Within the time-frequency resource grid corresponding to one symbol and one RB, the first CDM group occupies even-indexed subcarriers, such as subcarriers 0, 2, 4, 6, 8, and 10, and the second CDM group occupies odd-indexed subcarriers, such as subcarriers 1, 3, 5, 7, 9, and 11.

[0150] Compared to Type 1, Type 2 reduces the frequency domain density of DMRS. In this case, one antenna port has four REs within one RB for DMRS transmission. For Type 2, DMRS ports can be divided into three CDM groups, with code division multiplexing used between ports within each group. For example, a single-symbol DMRS supports a maximum of six antenna ports, divided into three CDM groups: {1000, 1001}, {1002, 1003}, and {1004, 1005}. A dual-symbol DMRS supports a maximum of twelve antenna ports, divided into three CDM groups: {1000, 1001, 1006, 1007}, {1002, 1003, 1008, 1009}, and {1004, 1005, 1010, 1011}.

[0151] For example, Figure 1F shows the time-frequency resources occupied by a dual-symbol DMRS Type 2. Within the time-frequency resource grid corresponding to one symbol and one RB, the first CDM group occupies subcarriers with indices 0, 1, 6, and 7, the second CDM group occupies subcarriers with indices 2, 3, 8, and 9, and the third CDM group occupies subcarriers with indices 4, 5, 10, and 11.

[0152] As can be seen from the above introduction, for a single CDM group or a single port, whether it is Type 1 or Type 2, it occupies a portion of the subcarriers within an RB. Taking Figure 1E as an example, the subcarrier indices occupied by port 1000 are 0, 2, 4, 6, 8, and 10. To describe whether the subcarriers in an RB that do not carry DMRS are idle, or whether they carry data (e.g., whether they carry the physical downlink shared channel (PDSCH)), the communication system defines the parameter "number of DMRS CDM groups without data". The functional description of the subcarriers within an RB under different numbers of DMRS CDM groups without data can be shown in Table 1.

[0153] Table 1

[0154] In a communication system, if a subcarrier is vacant, the power allocated to the vacant subcarrier can be superimposed on the DMRS sequence. For example, for type 1, port 1000, the subcarriers occupied are indices 0, 2, 4, 6, 8, and 10, meaning these subcarriers carry DMRS sequences. If the number of DMRS CDM groups without data is 2, the power superposition method is to increase the DMRS sequence power by 1 time (or 3 dB), which is beneficial for improving channel estimation performance.

[0155] In addition, the communication system defines the concepts of DMRS energy per resource element (EPRE), PDSCH EPRE, and physical uplink shared channel (PUSCH) EPRE, and gives the ratio of PDSCH / PUSCH EPRE to DMRS EPRE. This ratio is related to the number of DMRS CDM groups without data, as shown in Table 2.

[0156] Table 2

[0157] If the resource patterns occupied by DMRS and PDSCH are as shown in Figure 1G, and the PDSCH EPRE is the same as the DMRS EPRE, then their ratio is 1, or 0 dB. If the resource patterns occupied by DMRS and PDSCH are as shown in Figure 1H, and the PDSCH EPRE is 0.5 times the DMRS EPRE, then their ratio is 0.5, or -3 dB.

[0158] In some embodiments, PUSCH supports two waveforms: OFDM waveform and DFT-s-OFDM waveform. PDSCH supports OFDM waveform but not DFT-s-OFDM waveform.

[0159] In some embodiments, in the case of type 1, number of DMRS CDM groups without data = 1 or for type 2, number of DMRS CDM groups without data ≤ 2, the number of symbols occupied by PUSCH is less than or equal to 2, and the waveform adopts OFDM, while the number of symbols occupied by PDSCH is equal to 2 and adopts Type B mapping.

[0160] In some embodiments, when PUSCH uses a DFT-s-OFDM waveform, the DMRS sequence is generated based on the base sequence and supports type 1 DMRS. When the data uses... When the modulation and the length of the base sequence is greater than or equal to 30, the base sequence is obtained by modulating... The sequence is obtained by performing a DFT.

[0161] In related technologies, reference signals and data signals can be transmitted using time-division multiplexing. Taking the resources shown in Figure 1E as an example, in the frequency domain, the DMRS sequence corresponding to one antenna port occupies part of the subcarriers within one RB, while the data signal occupies all the subcarriers within one RB. In the time domain, the DMRS occupies symbols 2 and 3, and the data signal occupies all symbols except symbols 2 and 3. This approach results in low spectral efficiency. Therefore, a scheme using frequency-division multiplexing to transmit reference and data signals has been proposed. As shown in Figure 1I, the transmitter can perform a DFT on the modulated data signal, and then perform frequency domain multiplexing between the reference signal and the DFT-processed data signal to obtain the frequency domain signal. Taking a single-symbol Type 1 DMRS design as an example, the resource pattern occupied by the data signal and reference signal can be shown in Figure 1J. In Figure 1J, even-indexed subcarriers within one RB (such as subcarriers with indices 0, 2, 4, 6, 8, and 10) are used to carry DMRS, while the remaining subcarriers are used to carry data. This means the DMRS are evenly distributed across the frequency domain resources at a density of 1 / 2, or in other words, every other subcarrier carries DMRS, while data is placed between DMRS, or the frequency domain density of the DMRS is Δ = 2. Subsequently, the transmitter can perform operations such as IDFT on the obtained frequency domain signal. Since the data signal and reference signal occupy the same time domain resources, the receiver can demodulate the data promptly, thus reducing demodulation delay. However, this method results in a higher PAPR of the transmitted signal, leading to lower transmission power and affecting coverage.

[0162] For example, Figure 1K shows the PAPR when transmitting the data signal alone (or the DMRS alone) with Δ=2, a transmission bandwidth of 270RB, and an IDFT size of 4096, as well as the PAPR when the DMRS and data signals are frequency-division multiplexed. Figure 1K is based on the assumption that both the data signal and the DMRS use frequency division multiplexing. The plot is based on modulation as an example. Curve 101 represents the PAPR when transmitting the data signal alone (or transmitting the DMRS alone), and curve 102 represents the PAPR when the DMRS and data signals are frequency-division multiplexed. Obviously, the PAPR represented by curve 102 is higher than that represented by curve 101.

[0163] To address the aforementioned problems, this application provides a communication method. In this method, the transmitting end acquires a first reference signal sequence and a first data signal sequence. The first reference signal sequence is mapped to time units to obtain a first time-domain reference signal, and the first data signal sequence is mapped to time units to obtain a first time-domain data signal. The time units mapping the first reference signal sequence and the time units mapping the first data signal sequence do not overlap. Within the time units mapping the first reference signal sequence and the first data signal sequence, the absolute value of the phase difference between the mapped elements in any two adjacent time units is θ. The time-domain density of the first reference signal sequence is (1 / R), which is used to determine the number of time units mapping the first reference signal sequence. R is an integer greater than 2, and θ is not equal to 0. Subsequently, the transmitting end performs transform-domain precoding on the first time-domain reference signal and the first time-domain data signal respectively to obtain two sets of frequency-domain signals. These two sets of frequency-domain signals are interleaved and mapped to P frequency-domain units to obtain P frequency-domain signals. An inverse Fourier transform is performed on the P frequency-domain signals to obtain the signal to be transmitted, and the signal to be transmitted is then transmitted. In a sensing scenario, the signal, upon reaching the target, can be reflected by the target and received by the receiver. In a non-sensing scenario, the signal can be received by the receiver, which can also perform transform-domain precoding on the received signal to obtain two sets of frequency domain signals. One set of frequency domain signals includes the frequency domain signal corresponding to the first data signal sequence, and the other set includes the frequency domain signal corresponding to the first reference signal sequence. Subsequently, the receiver can perform channel equalization on the frequency domain signal corresponding to the first data signal sequence, perform inverse Fourier transform on the channel-equalized signal to obtain the first time-domain data signal, and obtain the first data signal sequence based on the first time-domain data signal.

[0164] In the above process, the transmitting end can map the first data signal sequence and the first reference signal sequence to different time domain and frequency domain positions, and perform transform domain precoding respectively, thereby enabling the signal to be transmitted to have single-carrier characteristics. Furthermore, in the time units of mapping the first data signal sequence and the first reference signal sequence, the absolute value of the phase difference between the mapped elements in any two adjacent time units is θ, which can reduce the envelope fluctuation of the signal to be transmitted. However, in the method shown in Figure 1I, frequency domain multiplexing of the data signal and reference signal destroys the single-carrier characteristics of the data signal. Therefore, the signal to be transmitted obtained by the method shown in Figure 1I does not have single-carrier characteristics and has a high PAPR. Therefore, the method provided in this application can reduce the PAPR of the signal to be transmitted. Utilizing this characteristic, after increasing the power of the signal to be transmitted, the signal is less prone to distortion, thereby improving coverage.

[0165] The method provided in this application can be used in various communication systems. For example, the communication system can be a Universal Mobile Telecommunications System (UMTS) system, a Long Term Evolution (LTE) system, a 5th Generation (5G) communication system, a Wireless Fidelity (WiFi) system, a 3rd Generation Partnership Project (3GPP) related communication system, a communication system evolving after 5G, or a system integrating multiple systems, etc., without limitation. Among them, 5G can also be referred to as New Radio (NR). The method provided in this application is described below using the communication system 1000 shown in Figure 2 as an example. Figure 2 is only a schematic diagram and does not constitute a limitation on the applicable scenarios of the technical solution provided in this application.

[0166] Figure 2 shows a schematic diagram of the architecture of the communication system 1000 provided in this application. In Figure 2, the communication system 1000 includes a RAN 100. The RAN 100 includes at least one RAN node (110a and 110b in Figure 2, collectively referred to as 110) and at least one terminal (120a-120j in Figure 2, collectively referred to as 120). The RAN 100 may also include other RAN nodes, such as wireless relay devices and / or wireless backhaul devices (not shown in Figure 2). The terminal 120 is wirelessly connected to the RAN node 110.

[0167] RAN 100 can be a 3GPP-related cellular system, such as a 4G, 5G mobile communication system, or a future-oriented evolution system. RAN 100 can also be an open access network (open RAN, O-RAN, or ORAN), a cloud radio access network (CRAN), or a WiFi system. RAN 100 can also be a communication system that integrates two or more of the above systems.

[0168] RAN node 110, sometimes also referred to as access network equipment, RAN entity, or access node, constitutes part of the communication system and is used to help terminals achieve wireless access. Multiple RAN nodes 110 in the communication system 1000 can be of the same type or different types.

[0169] In one possible scenario, a RAN node can be a base station, an evolved NodeB (eNodeB), a master eNodeB (MeNB), a secondary eNodeB (SeNB), a multi-standard radio (MSR) node, a home base station, a network controller, an access point (AP), a transmission reception point (TRP), a base station in a future mobile communication system, or an access node in a WiFi system. A RAN node can be a macro base station (as shown in Figure 2, 110a), a micro base station or indoor station (as shown in Figure 2, 110b), a relay node or donor node, or a radio controller in a CRAN scenario. Optionally, a RAN node can also be a server, wearable device, vehicle, or in-vehicle equipment. For example, the access network equipment in vehicle-to-everything (V2X) technology can be a roadside unit (RSU). In some scenarios, the roles of RAN node 110 and terminal 120 are relative. For example, a helicopter or drone that is usually configured as a terminal can also be configured as a mobile base station, and a device that accesses the RAN via a helicopter or drone is configured as a terminal.

[0170] In another possible scenario, multiple RAN nodes collaborate to assist the terminal in achieving wireless access, with different RAN nodes each implementing some of the base station's functions. Specifically, RAN nodes can be central units (CUs), distributed units (DUs), or radio units (RUs), etc. For example, a CU can perform the functions of the base station's radio resource control (RRC) layer and packet data convergence protocol (PDCP) layer. A CU can also perform the functions of the service data adaptation protocol (SDAP) layer. A DU can perform the functions of the base station's radio link control (RLC) layer and medium access control (MAC) layer. A DU can also perform some or all of the physical layer functions. An RU can be used to implement radio frequency signal transmission and reception. CUs and DUs can be set up separately or included in the same network element, such as a baseband unit (BBU). The RU can be included in radio frequency equipment or radio frequency units, such as in a remote radio unit (RRU), an active antenna unit (AAU), or a remote radio head (RRH). Furthermore, the CU can be further divided into the CU-control plane (CP) and the CU-user plane (UP).

[0171] In different systems, CU (or CU-CP and CU-UP), DU, or RU may have different names, but those skilled in the art will understand their meaning. For example, in an ORAN system, CU can also be called O-CU (open CU), DU can also be called O-DU, CU-CP can also be called O-CU-CP, CU-UP can also be called O-CU-UP, and RU can also be called O-RU. For ease of description, this application uses CU, CU-CP, CU-UP, DU, and RU as examples. Any of the units among CU (or CU-CP, CU-UP), DU, and RU in this application can be implemented through software modules, hardware modules, or a combination of software and hardware modules.

[0172] Terminal 120 is a device with wireless transceiver capabilities that can be deployed on land, including indoors, outdoors, handheld, or vehicle-mounted; it can also be deployed on water (such as on ships); and it can be deployed in the air (such as on airplanes, balloons, and satellites). A terminal can also be called a terminal device, which can be user equipment (UE), mobile station (MS), mobile terminal (MT), or a device used to provide voice or data connectivity to users, or a terminal in a future public land mobile network (PLMN). UEs include handheld devices with wireless communication capabilities, vehicle-mounted devices (e.g., cars, bicycles, electric vehicles, airplanes, ships, trains, high-speed trains), wearable devices (e.g., smartwatches, smart bracelets, pedometers), or computing devices. For example, a UE can be a mobile phone, tablet computer, laptop computer, PDA, mobile internet device (MID), satellite terminal, or computer with wireless transceiver capabilities. UE can also be a virtual reality (VR) terminal device, an augmented reality (AR) terminal device, a wireless modem, a point-of-sale (POS) machine, customer-premises equipment (CPE), a smart robot, a robotic arm, workshop equipment, smart home devices (e.g., refrigerators, televisions, air conditioners, electricity meters, etc.), a wireless terminal in industrial control, a wireless terminal in autonomous driving, a wireless terminal in telemedicine, a wireless terminal in a smart grid, a wireless terminal in transportation safety, a wireless terminal in intelligent transportation, a wireless terminal in a smart city, a wireless terminal in a smart home, an in-vehicle terminal, an RSU with terminal functionality, or flying equipment (e.g., a smart robot, a hot air balloon, a drone, an airplane), etc. A terminal can also be other devices with terminal functionality; for example, a terminal can be a device that acts as a terminal in device-to-device (D2D) communication.

[0173] By way of example and not limitation, in this application, the terminal can be a wearable device. Wearable devices, also known as wearable smart devices, are a general term for devices that utilize wearable technology to intelligently design and develop everyday wearables, such as glasses, gloves, watches, clothing, and shoes. Wearable devices are portable devices that are worn directly on the body or integrated into a user's clothing or accessories. For example, wearable devices are not merely hardware devices, but also devices that achieve powerful functions through software support, data interaction, and cloud interaction. Broadly speaking, wearable smart devices include devices that are feature-rich, large in size, and can achieve complete or partial functions without relying on a smartphone, such as smartwatches or smart glasses, as well as devices that focus on only one type of application function and need to be used in conjunction with other devices such as smartphones, such as various smart bracelets and smart jewelry for vital sign monitoring.

[0174] In this application, the terminal can be a terminal in an Internet of Things (IoT) system. IoT is an important component of future information technology development, and its main technical feature is connecting objects to networks through communication technologies, thereby realizing an intelligent network of human-machine interconnection and machine-to-machine interconnection. The terminal in this application can be a terminal in machine-type communication (MTC).

[0175] The terminal in this application can be an on-board module, on-board component, on-board chip, on-board unit (OBU), or telematics box (T-BOX) built into a vehicle as one or more components or units. The vehicle can implement the methods of this application through the built-in on-board module, on-board component, on-board chip, on-board unit, or T-BOX. The terminal can also be a complete vehicle device. Therefore, this application can be applied to vehicle networking, such as V2X, long-term evolution vehicle (LTE-V) communication technology, and vehicle-to-vehicle (V2V) communication.

[0176] It is understood that the communication system 1000 shown in Figure 2 is for illustrative purposes only and is not intended to limit the technical solutions of this application. Those skilled in the art should understand that in specific implementations, the communication system 1000 may also include other devices, and the number of RAN nodes and terminals may be determined according to specific needs without limitation.

[0177] Optionally, each network element or device (such as a RAN node or terminal) in Figure 2 of this application may also be referred to as a communication device, which may be a general-purpose device or a special-purpose device. This application does not make any specific limitation on this.

[0178] Optionally, the functions of each network element or device (e.g., RAN node or terminal) in Figure 2 of this application can be implemented by one device, multiple devices working together, or one or more functional modules within a single device. This application does not impose specific limitations on these functions. It is understood that the aforementioned functions can be network elements in hardware devices, software functions running on dedicated hardware, a combination of hardware and software, or virtualization functions instantiated on a platform (e.g., a cloud platform).

[0179] In practical implementation, each network element or device (e.g., RAN node or terminal) in Figure 2 of this application can adopt the composition structure shown in Figure 3, or include the components shown in Figure 3. Figure 3 shows a schematic diagram of the hardware structure of a communication device applicable to this application. It is understood that the communication device 30 includes means of necessary forms such as modules, units, elements, circuits, or interfaces, which are appropriately configured together to execute the solution provided in this application. For example, the communication device 30 includes one or more processors 301 for implementing the method provided in this application.

[0180] Processor 301 can be a general-purpose processor or a dedicated processor. For example, processor 301 can be a baseband processor or a central processing unit (CPU). The baseband processor can be used to process communication protocols and communication data, while the CPU can be used to control the communication device 30 (such as a RAN node, terminal, or chip), execute software programs, and process data from the software programs. Optionally, in one design, processor 301 may include program 305 (sometimes also referred to as code or instructions), which can be run on processor 301 to cause the communication device 30 to perform the methods described in the embodiments below. In yet another possible design, communication device 30 includes circuitry (not shown in FIG3) for implementing the functions of a transmitting or receiving end in the embodiments below.

[0181] Optionally, the communication device 30 may include one or more memories 303. The memory 303 may be a read-only memory (ROM) or other type of static storage device capable of storing static information and instructions, random access memory (RAM), cache, or other type of dynamic storage device capable of storing information and instructions. It may also be an electrically erasable programmable read-only memory (EEPROM), a compact disc read-only memory (CD-ROM) or other optical disc storage, optical disc storage (including compressed optical discs, laser discs, optical discs, digital universal optical discs, Blu-ray discs, etc.), magnetic disk storage media, or other magnetic storage devices, or any other medium capable of carrying or storing desired program code in the form of instructions or data structures and accessible by a computer, but is not limited thereto. The memory provided in this application may generally be non-volatile. Optionally, the memory 303 stores a program 307 (sometimes referred to as code or instructions), which can be executed on the processor 301 to cause the communication device 30 to perform the methods described in the following method embodiments. Optionally, the memory 303 may also be located outside the communication device 30.

[0182] Optionally, the processor 301 may include an AI module 306, and / or the memory 303 may include an AI module 308. The aforementioned AI modules are used to implement AI-related functions. The AI ​​modules can be implemented through software, hardware, or a combination of both. For example, the AI ​​module may include a RIC module. For example, the AI ​​module can be a near real-time RIC or a non-real-time RIC.

[0183] Optionally, data may also be stored in the processor 301 and / or the memory 303. The processor 301 and the memory 303 may be configured separately or integrated together.

[0184] Optionally, the communication device 30 may also include a transceiver 302 and / or an antenna 304. The processor 301, sometimes referred to as a processing unit, controls the communication device 30. The transceiver 302, sometimes referred to as a transceiver unit, transceiver, transceiver circuit, or transceiver, is used to realize the transmission and reception functions of the communication device 30 through the antenna 304.

[0185] It is understood that the composition shown in Figure 3 does not constitute a limitation on the communication device. In addition to the components shown in Figure 3, the communication device may include more or fewer components than shown, or combine certain components, or have different component arrangements.

[0186] The method provided in this application will now be described with reference to the accompanying drawings, taking a non-perceptual scenario as an example. Each network element in the following embodiments may have the components shown in Figure 3, which will not be elaborated upon further.

[0187] It is understood that in this application, the sending end and / or receiving end may perform some or all of the steps in this application. These steps are merely examples, and this application may also perform other steps or variations thereof. Furthermore, the steps may be performed in different orders as presented in this application, and it is not necessary to perform all the steps in this application.

[0188] It is understood that the methods described below in this application use the sending end and receiving end as examples to illustrate the interaction, but this application does not limit the execution subject of the interaction. For example, the sending end in the methods provided in the embodiments of this application can also be a chip, chip system, or processor that supports the sending end in implementing the method, or it can be a logic node, logic module, or software that can implement all or part of the sending end's functions; the receiving end in the methods provided below in this application can also be a chip, chip system, or processor that supports the receiving end in implementing the method, or it can be a logic node, logic module, or software that can implement all or part of the receiving end's functions.

[0189] As shown in Figure 4, a communication method provided in this application may include the following steps:

[0190] S401: The transmitting end acquires the first reference signal sequence and the first data signal sequence, and maps the two sequences to time units respectively to obtain the first time-domain reference signal and the first time-domain data signal.

[0191] In this application, the transmitting end can be any RAN node or terminal in the communication system 1000 shown in Figure 2.

[0192] In this application, the reference signal generated by the first reference signal sequence can be DMRS, SRS, CSI-RS, or TRS, etc., without limitation. The first data signal sequence is data in a data channel or control channel. The data channel is, for example, a physical uplink shared channel (PUSCH) or a physical downlink shared channel (PDSCH). The control channel is, for example, a physical uplink control channel (PUCCH).

[0193] In this application, the modulation scheme of the first data signal sequence and the modulation scheme of the first reference signal sequence can be the same or different. For example, the first reference signal sequence uses... The first data signal sequence is obtained by modulating a preset bit sequence. The data is obtained by modulating the data bit sequence. Alternatively, the first reference signal sequence is obtained by modulating a preset bit sequence using BPSK, and the first data signal sequence is obtained by modulating the data bit sequence using BPSK. Alternatively, the first reference signal sequence is obtained by using... The first data signal sequence is obtained by modulating a preset bit sequence using BPSK modulation. Alternatively, the first reference signal sequence is obtained by modulating a preset bit sequence using BPSK modulation, and the first data signal sequence is obtained by using... It is obtained by modulating the data bit sequence. The preset bit sequence can be a pseudo-random sequence, such as the Gold sequence or the Golay sequence.

[0194] In this application, in order to ensure that the signal to be transmitted obtained by processing the above two sets of sequences (i.e., the first reference signal sequence and the first data signal sequence) has single-carrier characteristics, the following constraint can be imposed on the two sets of sequences: the time unit occupied by the first reference signal sequence (i.e., the time unit for mapping the first reference signal sequence) does not overlap with the time unit occupied by the first data signal sequence (i.e., the time unit for mapping the first data signal sequence).

[0195] Any time unit in this application is a segment of resource in the time domain. For example, the time unit occupied by the first reference signal sequence includes the time unit occupied by each element in the first reference signal sequence. The time unit occupied by the first data signal sequence includes the time unit occupied by each element in the first data signal sequence.

[0196] In this application, mapping a first reference signal sequence to a time unit yields a first time-domain reference signal, and mapping a first data signal sequence to a time unit yields a first time-domain data signal. If the first time-domain reference signal is used... This indicates that the first time-domain data signal is used Indicate, then as well as The following relationship can be satisfied:

[0197] As can be seen, the above constraints allow the first reference signal sequence and the first data signal sequence to be transmitted in a time-division multiplexing manner.

[0198] In this application, in order to reduce the PAPR of the signal to be transmitted, the following constraints can be imposed on the first reference signal sequence and the first data signal sequence: in the time unit of mapping the first reference signal sequence and the first data signal sequence, the absolute value of the phase difference between the elements mapped in any two adjacent time units is θ, and θ is not equal to 0.

[0199] Understandable, if using express and The sequence formed, such as The above constraints can then be expressed as In this configuration, the absolute value of the phase difference between any two adjacent elements is θ. This reduces the envelope ripple of the transmitted signal, resulting in a lower PAPR. Here, θ can be equal to π / 2. In this case, the transmitted signal can achieve a PAPR similar to... The PAPR is the same as that of the DFT-s-OFDM signal.

[0200] Furthermore, this application does not limit the time-domain density of the first reference signal sequence. The time-domain density of the first reference signal sequence is used to determine the number of time units occupied by the first reference signal sequence (i.e., the number of time units mapping the first reference signal sequence).

[0201] For example, taking a first reference signal sequence uniformly distributed in the time domain as an example, the time domain density of the first reference signal sequence is (1 / R), where R is an integer greater than 1. For instance, when R equals 2, it means that in the first time domain reference signal, one time unit out of every two time units carries an element of the first reference signal sequence; when R equals 3, it means that one time unit out of every three time units carries an element of the first reference signal sequence; when R equals 4, it means that one time unit out of every four time units carries an element of the first reference signal sequence; when R equals 5, it means that one time unit out of every five time units carries an element of the first reference signal sequence, and so on. When R equals 2, 3, 4, or 5, the time units occupied by the reference signal can be as shown in Figure 5A.

[0202] It is understood that the above example is based on the case where the first reference signal sequence is uniformly arranged in the time domain. In specific applications, the first reference signal sequence may also be non-uniformly arranged in the time domain, and this application does not impose any restrictions.

[0203] One possible design, when R equals 3 or 5, is that the first reference signal sequence is The sequence, that is, the first reference signal sequence, is adopted. It is obtained by modulating a preset bit sequence. When R equals 4, the first reference signal sequence is a BPSK sequence, that is, the first reference signal sequence is obtained by modulating the preset bit sequence using BPSK.

[0204] One possible design is that any two elements in the first reference signal sequence have the same magnitude, and any two elements in the first data signal sequence have the same magnitude, in order to further reduce the PAPR of the signal to be transmitted.

[0205] One possible design is that the modulus of the elements in the first reference signal sequence is the same as the modulus of the elements in the first data signal sequence, in order to further reduce the PAPR of the signal to be transmitted.

[0206] The following uses the time-domain densities of the first reference signal sequence as (1 / 2), (1 / 3), (1 / 4), and (1 / 5) as examples to illustrate the time units occupied by the first reference signal sequence and the first data signal sequence, as shown in Figures 6A to 6D. In Figures 6A to 6D, I represents a real number, and jQ represents a purely imaginary number; or both I and jQ represent complex numbers, and the absolute value of the phase difference between them is 90 degrees.

[0207] In Figure 6A, the time-domain density of the first reference signal sequence is (1 / 2), and the length of the first reference signal sequence is... The length of the first data signal sequence is also (such as carrying) (bits). For example, the first reference signal sequence is {I, I, I, ...}, and the number of time units occupied by this sequence is... The index of the specific time unit occupied is The first data signal sequence is {jQ, jQ, jQ, ...}, and the number of time units occupied by this sequence is... The index of the specific time unit occupied is The first time-domain reference signal is {I, 0, I, 0, I, 0, ...}, and the first time-domain data signal is {0, jQ, 0, jQ, 0, jQ, ...}. The sequence formed by the first time-domain reference signal and the first time-domain data signal... Given {I, jQ, I, jQ, I, jQ, ...}, the length of this sequence is... The phase difference between any two adjacent elements in this sequence is π / 2. It should be understood that, in practical applications, the index of the time unit occupied by the first reference signal sequence can also be... The index of the time unit occupied by the first data signal sequence can also be... This application is not restricted.

[0208] In Figure 6B, the time-domain density of the first reference signal sequence is (1 / 3), and the length of the first reference signal sequence is... The length of the first data signal sequence is (such as carrying) (bits). For example, the first reference signal sequence is {I, jQ, I, jQ, ...}, and the number of time units occupied by this sequence is... The specific time unit indices are 0, 3, 6, 9…, and the first data signal sequence is {jQ, I, I, jQ, jQ, I, I, jQ, …}. The number of time units occupied by this sequence is… The specific time unit indices are 1, 2, 4, 5, 7, 8, 10, 11… The first time-domain reference signal is {I, 0, 0, jQ, 0, 0, I, 0, 0, jQ, 0, 0, …}, and the first time-domain data signal is {0, jQ, I, 0, I, jQ, 0, jQ, I, 0, I, jQ, …}. The sequence composed of the first time-domain reference signal and the first time-domain data signal… Given the sequence {I, jQ, I, jQ, I, jQ, I, jQ, I, jQ, I, jQ, ...}, the length of this sequence is... The phase difference between any two adjacent elements in this sequence is π / 2. In the example above, time unit 0 is occupied by the first reference signal sequence. It should be understood that in specific applications, time unit 0 can also be occupied by the first data signal sequence. For example, the indices of the time units occupied by the first data signal sequence are 0, 1, 3, 4, 6, 7, 9, 10…, and the indices of the time units occupied by the first reference signal sequence are 2, 5, 8, 11…

[0209] In Figure 6C, the time-domain density of the first reference signal sequence is (1 / 4), and the length of the first reference signal sequence is... The length of the first data signal sequence is (such as carrying) (bits). For example, the first reference signal sequence is {I, I, I, I, ...}, and the number of time units occupied by this sequence is... The specific time unit indices are 0, 4, 8, 12… The first data signal sequence is {jQ, I, jQ, jQ, I, jQ, jQ, I, jQ, jQ, I, jQ…}, and the number of time units occupied by this sequence is… The specific time unit indices are 1, 2, 3, 5, 6, 7, 9, 10, 11, 13, 14, 15… The first time-domain reference signal is {I, 0, 0, 0, I, 0, 0, 0, I, 0, 0, 0, I, 0, 0, 0, …}, and the first time-domain data signal is {0, jQ, I, jQ, 0, jQ, I, jQ, 0, jQ, I, jQ, 0, jQ, I, jQ, …}. The sequence formed by the first time-domain reference signal and the first time-domain data signal… is {I,jQ,I,jQ,I,jQ,I,jQ,I,jQ,I,jQ,I,jQ,I,jQ,…}, the length of the sequence is The phase difference between any two adjacent elements in this sequence is π / 2. In the example above, time unit 0 is occupied by the first reference signal sequence. It should be understood that in specific applications, time unit 0 can also be occupied by the first data signal sequence. For example, the indices of the time units occupied by the first data signal sequence are 0, 1, 2, 4, 5, 6, 8, 9, 10, 12, 13, 14…, and the indices of the time units occupied by the first reference signal sequence are 3, 7, 11, 15…

[0210] In Figure 6D, the time-domain density of the first reference signal sequence is (1 / 5), and the length of the first reference signal sequence is... The length of the first data signal sequence is (such as carrying) (bits). For example, the first reference signal sequence is {i, j, i, j, ...}, and the number of time units occupied by this sequence is... The specific time unit indices are 0, 5, 10, 15… The first data signal sequence is {j, i, j, i, i, j, i, j, j, i, j, i, j, i, j, i, j…}, and the number of time units occupied by this sequence is… The specific time unit indices are 1, 2, 3, 4, 6, 7, 8, 9, 11, 12, 13, 14, 16, 17, 18, 19… The first time-domain reference signal is {i, 0, 0, 0, 0, j, 0, 0, 0, 0, i, 0, 0, 0, 0, j, 0, 0, 0, 0…}, and the first time-domain data signal is {0, j, i, j, i, 0, i, j, i, j, 0, j, i, j, i, j, 0, i, j, i, j…}. The sequence formed by the first time-domain reference signal and the first time-domain data signal… Given the sequence {i, j, i, j, i, j, i, j, i, j, i, j, i, j, i, j, i, j, i, j…}, the length of this sequence is… The phase difference between any two adjacent elements in this sequence is π / 2. In the example above, time unit 0 is occupied by the first reference signal sequence. It should be understood that in specific applications, time unit 0 can also be occupied by the first data signal sequence. For example, the indices of the time units occupied by the first data signal sequence are 0, 1, 2, 3, 5, 6, 7, 8, 10, 11, 12, 13, 15, 16, 17, 18…, and the indices of the time units occupied by the first reference signal sequence are 4, 9, 14, 19…

[0211] The examples above are all described with the starting time unit index being 0. In specific applications, the starting time unit index can also be 1 or other values, without restriction. Similarly, in the frequency domain, the starting frequency domain unit index can be 0, 1, or other values. This application describes it with the starting frequency domain unit index being 0. This is a unified explanation here, and will not be repeated hereafter.

[0212] S402: The transmitting end performs transform-domain precoding on the first time-domain reference signal and the first time-domain data signal respectively to obtain two sets of frequency-domain signals.

[0213] In this application, the transform domain precoding is an orthogonal transform, such as DFT, wavelet transform, or discrete cosine transform, etc., without limitation.

[0214] Understandably, when the transmitting end performs transform-domain precoding (such as DFT) on the signal, and then performs inverse transform-domain precoding (such as IDFT) on the resulting frequency domain signal, phase ramping (PR) is introduced, which increases the PAPR of the signal to be transmitted. Therefore, before performing transform-domain precoding, the transmitting end can perform phase rotation on the first time-domain reference signal or the first time-domain data signal to eliminate the effect of phase ramping.

[0215] One possible implementation is that the transmitting end performs phase rotation on the elements of the first time-domain reference signal to obtain a second time-domain reference signal, and then performs transform-domain precoding on both the second time-domain reference signal and the first time-domain data signal to obtain two sets of frequency-domain signals. Alternatively, the transmitting end performs phase rotation on the elements of the first time-domain data signal to obtain a second time-domain data signal, and then performs transform-domain precoding on both the first time-domain reference signal and the second time-domain data signal to obtain two sets of frequency-domain signals. By using these methods, after interleaving and mapping the two sets of frequency-domain signals, the absolute value of the phase difference between any two adjacent time units mapped in the time units occupied by the first data signal sequence and the first reference signal sequence remains θ, thus resulting in a low PAPR of the signal to be transmitted.

[0216] Understandably, whether a phase tilt is introduced into the first time-domain reference signal depends on whether the index of the smallest frequency domain cell occupied by the first reference signal sequence (hereinafter referred to as δ1) is equal to 0. Similarly, whether a phase tilt is introduced into the first time-domain data signal depends on whether the index of the smallest frequency domain cell occupied by the first data signal sequence (hereinafter referred to as δ2) is equal to 0. Here, a frequency domain cell is a segment of resources occupied in the frequency domain. For example, a frequency domain cell includes at least one subcarrier or at least one RE, etc.

[0217] As an example, when δ1 = 0 and δ2 ≠ 0, a phase tilt is not introduced into the first time-domain reference signal, but a phase tilt is introduced into the first time-domain data signal. Therefore, the transmitting end performs phase rotation on the elements in the first time-domain data signal to obtain the second time-domain data signal, and performs transform-domain precoding on the first time-domain reference signal and the second time-domain data signal respectively to obtain two sets of frequency-domain signals. For example, in Figures 6B to 6D, the RE with the smallest index occupied by the first reference signal sequence is RE 0 (i.e., δ1 = 0), and the RE with the smallest index occupied by the first digital signal sequence is RE 1 (i.e., δ2 = 1). Therefore, the transmitting end performs phase rotation on the first time-domain data signal but not on the first time-domain reference signal.

[0218] As another example, when δ1≠0 and δ2=0, the first time domain data signal will not be introduced with phase tilt, but the first time domain reference signal will be introduced with phase tilt. Therefore, the transmitting end performs phase rotation on the elements in the first time domain reference signal to obtain the second time domain reference signal, and performs transform domain precoding on the second time domain reference signal and the first time domain data signal respectively to obtain two sets of frequency domain signals.

[0219] As is understood, in this application, phase rotation of the first time-domain data signal means multiplying each element of the first time-domain data signal by a corresponding phase rotation factor, such as multiplying the x-th element of the first time-domain data signal by... Where n is related to x, for example, n = x + a, where a is an integer. Similarly, in this application, phase rotation of the first time-domain reference signal means multiplying each element of the first time-domain reference signal by a corresponding phase rotation factor, such as multiplying the y-th element of the first time-domain reference signal by a... Here, m is related to y, for example, m = y + b, where b is an integer.

[0220] Understandably, the transmitting end may also choose not to perform phase rotation on the first time-domain reference signal and the first time-domain data signal. For example, the transmitting end can employ a suitable modulation scheme so that the first time-domain reference signal and the first time-domain data signal obtained after modulation and resource mapping can eliminate the effects of phase tilt. For example, the first time-domain reference signal and the first time-domain data signal shown in Figure 6A can be obtained without phase rotation. In Figure 6A, the first reference signal sequence is obtained by modulating a preset bit sequence using BPSK, that is, the first reference signal sequence is a BPSK sequence. The first data signal sequence is obtained by modulating the data bit sequence using phase-rotated BPSK (rotate BPSK), that is, the first data signal sequence is a rotated BPSK sequence.

[0221] S403: The transmitting end interleaves and maps the two sets of frequency domain signals to P frequency domain units to obtain P frequency domain signals.

[0222] In this application, P represents the number of frequency domain units included in the transmission bandwidth. P is greater than or equal to twice the sum of the lengths of the first reference signal sequence and the first data signal sequence, that is, P is greater than or equal to N. SC For ease of description, the following embodiments of this application use P equal to N. SC Let's take an example to describe it.

[0223] Understandably, this application does not limit the frequency domain density of the first reference signal sequence. The frequency domain density of the first reference signal sequence is used to determine the number of frequency domain units occupied by the first reference signal sequence.

[0224] For example, taking a first reference signal sequence uniformly distributed in the frequency domain as an example, the frequency domain density of the first reference signal sequence is (1 / Δ), where Δ is an integer greater than 1. For example, when Δ equals 2, it means that one out of every two frequency domain units carries the reference signal; when Δ equals 3, it means that one out of every three frequency domain units carries the reference signal; when Δ equals 4, it means that one out of every four frequency domain units carries the reference signal, and so on. When Δ equals 2, 3, or 4, the frequency domain units occupied by the reference signal can be as shown in Figure 5B.

[0225] Understandably, reference signals can be used for channel estimation, and better channel estimation performance can be obtained when the reference signals are uniformly distributed in the frequency domain. However, in specific applications, the first reference signal sequence can also be non-uniformly distributed in the frequency domain, and this application does not impose any restrictions.

[0226] One possible implementation is that the transmitter maps one of the two sets of frequency domain signals to the 2p-th frequency domain cell out of P frequency domain cells, and maps the other set of frequency domain signals to the (2p+1)-th frequency domain cell out of P frequency domain cells. Here, p is greater than or equal to 0 and less than... integers, This indicates rounding down. In this way, the data signal can be evenly distributed across P frequency domain units to maximize the channel frequency selectivity gain.

[0227] Understandably, through S402, the two sets of frequency domain signals obtained by the transmitting end are the frequency domain signal group corresponding to the reference signal (hereinafter referred to as the first frequency domain signal group) and the frequency domain signal group corresponding to the data signal (hereinafter referred to as the second frequency domain signal group). The transmitting end can map the first frequency domain signal group to the 2p-th frequency domain unit in P frequency domain units, and map the second frequency domain signal group to the (2p+1)-th frequency domain unit in P frequency domain units. For example, the frequency domain unit indices occupied by the frequency domain signals in the first frequency domain signal group are 0, 2, 4, 6, 8..., and the frequency domain unit indices occupied by the frequency domain signals in the second frequency domain signal group are 1, 3, 4, 7, 9... Alternatively, the transmitting end can map the second frequency domain signal group to the 2p-th frequency domain unit in P frequency domain units, and map the first frequency domain signal group to the (2p+1)-th frequency domain unit in P frequency domain units. For example, the frequency domain cells occupied by the frequency domain signals in the second frequency domain signal group are 0, 2, 4, 6, 8..., and the frequency domain cells occupied by the frequency domain signals in the first frequency domain signal group are 1, 3, 4, 7, 9...

[0228] Understandably, in the above example, Δ equals 2. Figure 6A is drawn with the frequency domain cell indices of the frequency domain signals in the second frequency domain signal group being 0, 2, 4, 6, 8, and 10, and the frequency domain cell indices of the frequency domain signals in the first frequency domain signal group being 1, 3, 4, 7, 9, and 11 as an example. Figures 6B to 6D are drawn with the frequency domain cell indices of the frequency domain signals in the first frequency domain signal group being 0, 2, 4, 6, 8..., and the frequency domain cell indices of the frequency domain signals in the second frequency domain signal group being 1, 3, 4, 7, 9... as an example.

[0229] S404: The transmitting end performs inverse Fourier transform on P frequency domain signals to obtain the signal to be transmitted.

[0230] One possible implementation involves the transmitter performing P-point IDFT and cyclic prefix operations on P frequency domain signals to obtain the signal to be transmitted. Specifically, this can be illustrated in Figures 6A to 6D.

[0231] Optionally, to reduce PAPR, the transmitting end can perform spectrum shaping on the P frequency domain signals, and then perform an inverse Fourier transform on the spectrum-shaped signals to obtain the signal to be transmitted. Understandably, when P is greater than twice the sum of the lengths of the first reference signal sequence and the first data signal sequence, the PAPR reduction effect is better.

[0232] S405: The transmitting end sends the signal to be transmitted to the receiving end. Correspondingly, the receiving end receives the signal sent by the transmitting end.

[0233] In this application, the receiving end can be a RAN node or terminal in the communication system 1000 shown in Figure 2 that is communicatively connected to the transmitting end. For example, when the transmitting end is RAN node 110a in Figure 2, the receiving end is any terminal accessing RAN node 110a, such as terminal 120a or terminal 120i; or, when the transmitting end is terminal 120f in Figure 2, the receiving end is a RAN node that provides services to terminal 120f, such as RAN node 110b; or, both the transmitting end and the receiving end are terminals, such as the transmitting end being terminal 120i and the receiving end being terminal 120j.

[0234] Understandably, the receiver can perform the inverse operation of the transmitter on the received signal to obtain the data signal. Furthermore, the receiver can extract a reference signal for operations such as channel estimation. For example, the receiver can perform the following steps:

[0235] S406: The receiver performs transform domain precoding on the received signal to obtain two sets of frequency domain signals.

[0236] Understandably, of the two sets of frequency domain signals, one set includes the frequency domain signal corresponding to the first data signal sequence, and the other set includes the frequency domain signal corresponding to the first reference signal sequence. It should be understood that these two sets of frequency domain signals are interleaved and mapped in the frequency domain. In the time domain, the time units mapping the first data signal sequence and the time units mapping the first reference signal sequence do not overlap. Within the time units occupied by the mapping of the first data signal sequence and the first reference signal sequence, the absolute value of the phase difference between the mapped elements in any two adjacent time units is θ. The time domain density of the first reference signal sequence is (1 / R), and the frequency domain density of the first reference signal sequence is (1 / Δ).

[0237] Understandably, if the transmitting end performs the operation of adding a cyclic prefix, before S406, the receiving end can perform the operation of removing the cyclic prefix on the received signal.

[0238] S407: The receiver performs channel equalization on the frequency domain signal corresponding to the first data signal sequence, and performs inverse Fourier transform on the channel-equalized signal to obtain the first time domain data signal.

[0239] Understandably, in the first time-domain data signal, the absolute value of the phase difference between any two adjacent elements is θ or 0.

[0240] Understandably, if the reference signal is used for channel estimation, the receiver can also extract the reference signal from the frequency domain signal corresponding to the first reference signal sequence, perform channel estimation, and interpolate to obtain the channel information of the data signal. In this application, the time-frequency resources occupied by the reference signal can be defined in the protocol, negotiated between the transmitter and receiver, indicated by the transmitter to the receiver, or indicated by the receiver to the transmitter; there are no restrictions. Subsequently, the receiver can perform channel equalization on the frequency domain signal corresponding to the first data signal sequence based on the channel estimation result, and perform an inverse Fourier transform on the channel-equalized signal to obtain the first time-domain data signal.

[0241] S408: The receiving end obtains the first data signal sequence based on the first time domain data signal.

[0242] Understandably, the receiving end can also obtain the data bit sequence based on the first data signal sequence.

[0243] Based on the method shown in Figure 4, the transmitting end can map the first data signal sequence and the first reference signal sequence to different time and frequency domain positions, and perform transform-domain precoding, thereby enabling the signal to be transmitted to possess single-carrier characteristics. Furthermore, within the time units occupied by the first data signal sequence and the first reference signal sequence, the absolute value of the phase difference between any two adjacent time units is θ, which can reduce the envelope fluctuation of the signal to be transmitted. Therefore, the method shown in Figure 4 can reduce the PAPR of the signal to be transmitted (e.g., by achieving a PAPR of θ). The DFT-s-OFDM signal has the same PAPR. Utilizing this characteristic, the signal is less prone to distortion after the power of the signal to be transmitted is increased, thereby improving coverage. Furthermore, in the method shown in Figure 4, spectral efficiency can be improved by adjusting the value of R. For example, in Figure 6A, R equals 2, and the length of the first data signal sequence is... That is, through the processing method shown in Figure 6A, the sending end can transmit... The data consists of bits. In Figure 6B, R equals 3, and the length of the first data signal sequence is . That is, through the processing method shown in Figure 6B, the sending end can transmit... 1 bit of data. In Figure 6C, R equals 4, and the length of the first data signal sequence is 1. That is, through the processing method shown in Figure 6C, the sending end can transmit... 1 bit of data. In Figure 6D, R equals 5, and the length of the first data signal sequence is 1. That is, through the processing method shown in Figure 6D, the sending end can transmit... The data consists of 10 bits. It is evident that as R increases, the amount of data transmitted by the transmitter increases, which can improve spectral efficiency.

[0244] Optionally, in one possible implementation of the method shown in Figure 4, the transmitting end can acquire the first data signal sequence at least through method 1 or method 2.

[0245] Method 1: Obtaining data from the sending end Sequence, pair The elements in the sequence are transposed and / or phase rotated to obtain the first data signal sequence.

[0246] For example, taking R equal to 3, the sending end can use... Modulate the data bit sequence to obtain a length of of The sequence is {d(n)}. Subsequently, the transmitting end performs the following transposition and phase rotation operations on {d(n)} to obtain the first data signal sequence.

[0247] Where, Δ T =2, It is an integer.

[0248] For example, taking R equal to 3, the sending end can use... Modulate the bit sequence to obtain a length of of The sequence is {d(n)}. Subsequently, the transmitting end performs the following transposition operation on {d(n)} to obtain the first data signal sequence.

[0249] Where m equals 0 or 1, It is an integer.

[0250] For example, taking R equal to 5, the sending end can use... Modulate the bit sequence to obtain a length of of The sequence is {d(n)}. Subsequently, after the transmitting end performs the transposition and phase rotation operations on {d(n)} as shown in formula (1) above, the first data signal sequence can be obtained. In this example, Δ T =4, It is an integer.

[0251] For example, taking R equal to 4, the sending end can use... Modulate the bit sequence to obtain a length of of The sequence is {d(n)}. Subsequently, after the transmitting end performs the transposition and phase rotation operations on {d(n)} as shown in formula (1) above, the first data signal sequence can be obtained. In this example, Δ T =3, It is an integer.

[0252] For example, taking R equal to 4, the sending end can use... Modulate the bit sequence to obtain a length of of The sequence is {d(n)}. Subsequently, the transmitting end performs the following transposition operation on {d(n)} to obtain the first data signal sequence.

[0253] Where m equals 0, 1, or 2. It is an integer.

[0254] For example, taking R equal to 2, the sending end can use... Modulate the bit sequence to obtain a length of of The sequence is {d(n)}. Subsequently, the sending end can perform a phase rotation operation on {d(n)}, such as multiplying the z-th element of {d(n)} by... Here, k is related to z, for example, k = z + c, where c is an integer.

[0255] Method 2: The transmitting end acquires multiple BPSK sequences and obtains the first data signal sequence based on these multiple BPSK sequences.

[0256] For example, the first data signal sequence shown in Figure 6B can be obtained based on two BPSK sequences, one of which is {jQ, jQ, jQ, jQ, ...} and the other is {I, I, I, I, ...}. The constellations corresponding to these two BPSK sequences have a 90-degree phase difference. After obtaining these two BPSK sequences, the transmitting end inserts one BPSK sequence into the other to obtain the first data signal sequence. Understandably, the first data signal sequence shown in Figure 6C can be processed similarly.

[0257] For example, the first data signal sequence shown in Figure 6D can be obtained based on two BPSK sequences, one of which is {j, j, j, j, ...} and the other is {i, i, i, i, ...}. The constellations corresponding to these two BPSK sequences have a 90-degree phase difference. After obtaining these two BPSK sequences, the transmitting end inserts one BPSK sequence into the other to obtain the first data signal sequence.

[0258] Understandably, the receiving end needs to perform the inverse operation corresponding to that performed at the transmitting end on the received signal. Therefore, when the transmitting end obtains the first data signal sequence in the above manner, in S408, the receiving end can perform the corresponding inverse operation on the first data signal sequence to obtain... Sequence (or BPSK sequence), and then based on The sequence (or BPSK sequence) is used to obtain the data bit sequence.

[0259] For example, when the transmitting end processes the signal using formula (1), the receiving end can perform the following transposition and phase rotation operations on the first data signal sequence to obtain... sequence:

[0260] Optionally, in one possible implementation of the method shown in Figure 4, the ratio of the EPRE corresponding to the first data signal sequence to the EPRE corresponding to the first reference signal sequence (referred to as the first ratio) is related to R. Thus, the receiver can determine the first ratio based on R and then perform coherent data demodulation. Therefore, the transmitter and receiver do not need to exchange the first ratio, thereby reducing signaling overhead.

[0261] For example, if the total energy of one reference signal symbol is N sc The number of subcarriers carrying the reference signal is The number of subcarriers carrying data signals is The total energy occupied by the first reference signal sequence is The total energy occupied by the first data signal sequence is Therefore, the EPRE corresponding to the first reference signal sequence is... The EPRE corresponding to the first data signal sequence is: It can be seen that, in the case of frequency division multiplexing of the first data signal sequence and the first reference signal sequence, the first ratio is Taking the resource shown in Figure 1J as an example, in the time domain, both the first reference signal sequence and the first data signal sequence are mapped to the first symbol in Figure 1J. In the frequency domain, the first reference signal sequence is mapped to subcarriers 0, 2, 4, 6, 8, and 10, and the first data signal sequence is mapped to subcarriers 1, 3, 5, 7, 9, and 11. At this point, the first ratio is R⁻¹. It can be understood that when R = 2, the first ratio is 1; when R = 3, the first ratio is 2; when R = 4, the first ratio is 3; and when R = 5, the first ratio is 4.

[0262] Furthermore, in non-frequency division multiplexing scenarios, the ratio of the EPRE corresponding to the data signal sequence to the EPRE corresponding to the reference signal sequence is also related to R. Taking the resource shown in Figure 1J as an example, in the time domain, the first reference signal sequence is mapped to the first symbol in Figure 1J, and the second data signal sequence is mapped to the second symbol in Figure 1J. In the frequency domain, the first reference signal sequence is mapped to subcarriers 0, 2, 4, 6, 8, and 10, and the first data signal sequence is mapped to all subcarriers on one RB. In this case, the ratio of the EPRE corresponding to the second data signal sequence to the EPRE corresponding to the first reference signal sequence (referred to as the second ratio) is: Understandably, when R = 2, the second ratio is 1. When R = 3, the second ratio is 1.5. When R = 4, the second ratio is 2. When R = 5, the second ratio is 2.5.

[0263] In summary, given a fixed R, either the sender or receiver can determine the first ratio and / or the second ratio. Therefore, no additional signaling is required between the sender and receiver to indicate these two ratios, saving signaling overhead.

[0264] Understandably, as mentioned earlier, as R increases, the amount of data (coded bits) transmitted by the transmitter increases, which can improve spectral efficiency. Furthermore, given a fixed number of information bits, increasing the amount of data (coded bits) transmitted by the transmitter helps reduce the code rate. However, as R gradually increases, it also reduces the EPRE corresponding to the first reference signal sequence, which degrades channel estimation. Therefore, in practical applications, R can be designed as needed to balance code rate and channel estimation performance. In addition, compared to the processing method shown in Figure 6A, the processing methods shown in Figures 6B to 6D offer gains in channels with less frequency selectivity (e.g., smaller multipath delay spread).

[0265] It is understood that the actions of the sending or receiving end in the above steps can be executed by the processor 301 in the communication device 30 shown in Figure 3, which calls the application code stored in the memory 303. This application does not impose any restrictions on this.

[0266] The various embodiments mentioned above in this application can be combined without contradiction, and no limitation is imposed.

[0267] The above mainly describes the solution provided in this application from the perspective of interaction between various network elements. Correspondingly, this application also provides a communication device, which can be the transmitting end in the above method embodiments, or a device including the transmitting end, or a component usable as a transmitting end; or, the communication device can be the receiving end in the above method embodiments, or a device including the receiving end, or a component usable as a receiving end. It is understood that the transmitting end or receiving end, etc., includes hardware structures and / or software modules corresponding to the execution of each function in order to achieve the above functions. Those skilled in the art should readily recognize that, based on the unit and algorithm operations of the various examples described in conjunction with the embodiments disclosed herein, this application can be implemented in hardware or a combination of hardware and computer software. Whether a function is executed by hardware or by computer software driving hardware depends on the specific application and design constraints of the technical solution. Those skilled in the art can use different methods to implement the described functions for each specific application, but such implementation should not be considered beyond the scope of this application.

[0268] This application can divide the sending or receiving end into functional modules based on the above method examples. For example, each function can be divided into its own functional module, or two or more functions can be integrated into one processing module. The integrated module can be implemented in hardware or as a software functional module. It is understood that the module division in this application is illustrative and only represents one logical functional division; other division methods may be used in actual implementation.

[0269] For example, when functional modules are integrated, Figure 7 shows a schematic diagram of a communication device 70. The communication device 70 includes a processing module 701 and an interface module 702. The processing module 701, also called a processing unit, is used to perform operations other than transmission and reception; for example, it can be a processing circuit or a processor. The interface module 702, also called an interface unit, is used to perform transmission and reception operations; for example, it can be an interface circuit, a transceiver, a transceiver unit, or a communication interface.

[0270] In some embodiments, the communication device 70 may further include a storage module (not shown in FIG. 7) for storing program instructions and data.

[0271] In some embodiments, the communication device 70 may further include an AI module (not shown in FIG. 7) for implementing AI-related functions. The AI ​​module can implement AI functions through software, hardware, or a combination of software and hardware. For example, the AI ​​module includes a RIC module. Optionally, the AI ​​module and the storage module are integrated into one module, or the AI ​​module and the processing module 701 are integrated into one module.

[0272] For example, the communication device 70 is used to implement the function of a transmitter. The communication device 70 is, for example, the transmitter described in the embodiment shown in FIG4.

[0273] The processing module 701 is used to acquire a first reference signal sequence and a first data signal sequence, and map the two sequences to time units respectively to obtain a first time-domain reference signal and a first time-domain data signal. For example, the processing module 701 can be used to execute S401.

[0274] The processing module 701 is also used to perform transform-domain precoding on the first time-domain reference signal and the first time-domain data signal respectively to obtain two sets of frequency-domain signals. For example, the processing module 701 can also be used to execute S402.

[0275] The processing module 701 is also used to interleave and map the two sets of frequency domain signals to P frequency domain units to obtain P frequency domain signals. For example, the processing module 701 can also be used to execute S403.

[0276] The processing module 701 is also used to perform inverse Fourier transform on the P frequency domain signals to obtain the signal to be transmitted. For example, the processing module 701 can also be used to execute S404.

[0277] Interface module 702 is used to send the signal to be sent. For example, interface module 702 can be used to execute S405.

[0278] When used to implement the function of the transmitting end, for other functions that the communication device 70 can implement, please refer to the relevant description of the embodiment shown in FIG4, which will not be elaborated further.

[0279] Alternatively, by way of example, the communication device 70 is used to implement the function of a receiving end. The communication device 70 is, for example, the receiving end described in the embodiment shown in FIG4.

[0280] The interface module 702 is used to receive signals sent by the transmitting end. For example, the interface module 702 can be used to execute S405.

[0281] Processing module 701 is used to perform transform-domain precoding on the received signal to obtain two sets of frequency domain signals. For example, processing module 701 can be used to execute S406.

[0282] The processing module 701 is further configured to perform channel equalization on the frequency domain signal corresponding to the first data signal sequence, and to perform inverse Fourier transform on the channel-equalized signal to obtain the first time domain data signal. For example, the processing module 701 may also be configured to execute S407.

[0283] The processing module 701 is further configured to obtain a first data signal sequence based on the aforementioned first time-domain data signal. For example, the processing module 701 may also be configured to execute S408.

[0284] When used to implement the function of the receiving end, other functions that the communication device 70 can implement can be referred to the relevant description of the embodiment shown in FIG4, which will not be elaborated further.

[0285] In a simplified embodiment, those skilled in the art will recognize that the communication device 70 can take the form shown in FIG3. For example, the processor 301 in FIG3 can invoke computer execution instructions stored in memory 303 to cause the communication device 70 to execute the method described in the above-described method embodiment.

[0286] For example, the functions / implementation processes of the processing module 701 and interface module 702 in FIG7 can be implemented by the processor 301 in FIG3 calling computer execution instructions stored in memory 303. Alternatively, the functions / implementation processes of the processing module 701 in FIG7 can be implemented by the processor 301 in FIG3 calling computer execution instructions stored in memory 303, and the functions / implementation processes of the interface module 702 in FIG7 can be implemented by the transceiver 302 in FIG3.

[0287] It is understood that one or more of the above modules or units can be implemented by software, hardware, or a combination of both. When any of the above modules or units are implemented by software, the software exists as computer program instructions and is stored in memory. The processor can be used to execute the program instructions and implement the above method flow. The processor can be built into a system-on-a-chip (SoC) or an application-specific integrated circuit (ASIC), or it can be a stand-alone semiconductor chip. In addition to the core that executes software instructions for computation or processing, the processor may further include necessary hardware accelerators, such as field-programmable gate arrays (FPGAs), programmable logic devices (PLDs), or logic circuits that implement dedicated logic operations.

[0288] When the above modules or units are implemented in hardware, the hardware can be any one or any combination of a CPU, microprocessor, digital signal processing (DSP) chip, microcontroller unit (MCU), artificial intelligence processor, ASIC, SoC, FPGA, PLD, application-specific digital circuit, hardware accelerator, or non-integrated discrete device, which can run the necessary software or perform the above method flow independently of software.

[0289] Optionally, this application also provides a chip system comprising: at least one processor and an interface, wherein the at least one processor is coupled to a memory via the interface, and when the at least one processor executes a computer program or instructions in the memory, the method in any of the above method embodiments is executed. In one possible implementation, the chip system further includes a memory, or the memory may be located outside the chip system. Optionally, the chip system may be composed of chips or may include chips and other discrete devices; this application does not specifically limit this.

[0290] Optionally, this application also provides a computer-readable storage medium. All or part of the processes in the above method embodiments can be implemented by a computer program instructing related hardware. This program can be stored in the aforementioned computer-readable storage medium. When executed, the program can include the processes described in the above method embodiments. The computer-readable storage medium can be an internal storage unit of the communication device in any of the foregoing embodiments, such as the hard disk or memory of the communication device. The aforementioned computer-readable storage medium can also be an external storage device of the communication device, such as a plug-in hard disk, smart media card (SMC), secure digital (SD) card, flash card, etc., equipped on the communication device. Further, the aforementioned computer-readable storage medium can include both internal storage units and external storage devices of the communication device. The aforementioned computer-readable storage medium is used to store the aforementioned computer program and other programs and data required by the communication device. The aforementioned computer-readable storage medium can also be used to temporarily store data that has been output or will be output.

[0291] Optionally, this application also provides a computer program product. All or part of the processes in the above method embodiments can be executed by a computer program instructing related hardware. This program can be stored in the above computer program product, and when executed, it can include the processes described in the above method embodiments.

[0292] Optionally, this application also provides computer instructions. All or part of the processes in the above method embodiments can be executed by computer instructions instructing related hardware (such as a computer, processor, terminal, or RAN node). The program can be stored in the aforementioned computer-readable storage medium or the aforementioned computer program product.

[0293] Optionally, this application also provides a communication system, including: the transmitting end and the receiving end in the above embodiments.

[0294] Through the above description of the embodiments, those skilled in the art can clearly understand that, for the sake of convenience and brevity, only the division of the above functional modules is used as an example. In actual applications, the above functions can be assigned to different functional modules as needed, that is, the internal structure of the device can be divided into different functional modules to complete all or part of the functions described above.

[0295] It is understood that the term "connection" in this application can refer to a direct connection or an indirect connection; furthermore, it can refer to an electrical connection or a communication connection. For example, the connection of two electrical components A and B can refer to a direct connection between A and B, or an indirect connection between A and B through other electrical components or connection media, enabling the transmission of electrical signals between A and B; similarly, the connection of two devices A and B can refer to a direct connection between A and B, or an indirect connection between A and B through other communication devices or communication media, enabling communication between A and B.

[0296] The method provided in this application can be applied to wireless communication between communication devices. Wireless communication between communication devices can include: wireless communication between RAN nodes and terminals, wireless communication between RAN nodes, wireless communication between terminals, wireless communication between RAN nodes and AI devices, and wireless communication between terminals and AI devices. In this application, the term "wireless communication" can also be abbreviated as "communication," and the term "communication" can also be described as "data transmission," "signal transmission," "information transmission," or "transmission."

[0297] It is understood that the message names between various network elements or the names of various parameters in the messages in the above embodiments of this application are just examples, and other names may be used in the specific implementation. This application does not make any specific limitations on this.

[0298] It is understood that in this application, " / " can indicate that the objects before and after it are in an "or" relationship. For example, A / B can mean A or B. "And / or" can be used to describe three relationships between the related objects. For example, A and / or B can mean: A exists alone, A and B exist simultaneously, and B exists alone. Here, A and B can be singular or plural. Furthermore, expressions like "at least one of A, B, and C" or "at least one of A, B, or C" are generally used to indicate any of the following: A exists alone; B exists alone; C exists alone; A and B exist simultaneously; A and C exist simultaneously; B and C exist simultaneously; A, B, and C exist simultaneously. The above examples using three elements (A, B, and C) illustrate the optional entries for this item. When the expression contains more elements, its meaning can be obtained according to the aforementioned rules.

[0299] To facilitate the description of the technical solutions of this application, the terms "first" and "second" may be used to distinguish technical features with the same or similar functions. The terms "first" and "second" do not limit the number or execution order, nor do they imply that they are necessarily different. In this application, the terms "exemplary" or "for example" are used to indicate examples, illustrations, or descriptions. Any embodiment or design scheme described as "exemplary" or "for example" should not be construed as being more preferred or advantageous than other embodiments or design schemes. The use of "exemplary" or "for example" is intended to present the relevant concepts in a concrete manner for ease of understanding.

[0300] It is understood that the term "embodiment" used throughout the specification means that a specific feature, structure, or characteristic related to an embodiment is included in at least one embodiment of this application. Therefore, various embodiments throughout the specification do not necessarily refer to the same embodiment. Furthermore, these specific features, structures, or characteristics can be combined in any suitable manner in one or more embodiments. It is understood that in the various embodiments of this application, the sequence number of each process does not imply a sequential order of execution; the execution order of each process should be determined by its function and internal logic, and should not constitute any limitation on the implementation process of this application.

[0301] It is understood that in this application, "when," "under the circumstances," "if," and "if" all refer to the corresponding processing that will be carried out under certain objective circumstances, and are not time-limited, nor do they require that there must be a judgment action when implemented, nor do they imply any other limitations.

[0302] In this application, "simultaneously" can be understood as at the same point in time, within a period of time, or within the same cycle.

[0303] In this application, "greater than or equal to" can be replaced with "greater than" or "equal to"; "less than or equal to" can be replaced with "less than" or "equal to". For example, "A is greater than or equal to B" can be replaced with "A is greater than B" or "A is equal to B"; "A is less than or equal to B" can be replaced with "A is less than B" or "A is equal to B".

[0304] It is understood that some optional features in this application can be implemented independently in certain scenarios without relying on other features, such as the current solution upon which they are based, to solve the corresponding technical problems and achieve the corresponding effects. Alternatively, they can be combined with other features as needed in certain scenarios. Correspondingly, the apparatus provided in this application can also implement these features or functions, which will not be elaborated here.

[0305] It is understood that the same step or step with the same function or technical feature in this application can be referenced and learned from each other in different embodiments.

[0306] In the several embodiments provided in this application, it should be understood that the disclosed apparatus and methods can be implemented in other ways. For example, the apparatus embodiments described above are merely illustrative; for instance, the division of modules or units is only a logical functional division, and in actual implementation, there may be other division methods. For example, multiple units or components may be combined or integrated into another device, or some features may be ignored or not executed. Furthermore, the mutual coupling or direct coupling or communication connection shown or discussed may be through some interfaces; the indirect coupling or communication connection between devices or units may be electrical, mechanical, or other forms.

[0307] The units described as separate components may or may not be physically separate. A component shown as a unit can be one or more physical units; that is, it can be located in one place or distributed in multiple different locations. Some or all of the units can be selected to achieve the purpose of this embodiment according to actual needs.

[0308] Furthermore, the functional units in the various embodiments of this application can be integrated into one processing unit, or each unit can exist physically separately, or two or more units can be integrated into one unit. The integrated unit can be implemented in hardware or as a software functional unit.

[0309] The above description is merely a specific embodiment of this application, but the scope of protection of this application is not limited thereto. Any changes or substitutions within the technical scope disclosed in this application should be included within the scope of protection of this application. Therefore, the scope of protection of this application should be determined by the scope of the claims.

Claims

1. A communication method, characterized in that, The method includes: Acquire the first reference signal sequence and the first data signal sequence; The first reference signal sequence is mapped to a time unit to obtain a first time-domain reference signal, and the first data signal sequence is mapped to a time unit to obtain a first time-domain data signal. The time units for mapping the first reference signal sequence and the time units for mapping the first data signal sequence do not overlap. In the time units for mapping the first reference signal sequence and the first data signal sequence, the absolute value of the phase difference between the elements mapped in any two adjacent time units is θ. The time-domain density of the first reference signal sequence is (1 / R). The time-domain density of the first reference signal sequence is used to determine the number of time units for mapping the first reference signal sequence. R is an integer greater than 2, and θ is not equal to 0. The first time-domain reference signal and the first time-domain data signal are respectively precoded in the transform domain to obtain two sets of frequency domain signals; The two sets of frequency domain signals are interleaved and mapped to P frequency domain units to obtain P frequency domain signals, where P is greater than or equal to twice the sum of the length of the first reference signal sequence and the length of the first data signal sequence. Perform an inverse Fourier transform on the P frequency domain signals to obtain the signal to be transmitted; Send the signal to be sent.

2. The method according to claim 1, characterized in that, The acquisition of the first data signal sequence includes: Get - Binary phase shift keying sequence; Regarding the - The elements in the binary phase shift keying sequence are transposed and / or phase rotated to obtain the first data signal sequence.

3. The method according to claim 1, characterized in that, The acquisition of the first data signal sequence includes: Obtain multiple binary phase shift keying sequences; The first data signal sequence is obtained based on the plurality of binary phase shift keying sequences.

4. The method according to any one of claims 1-3, characterized in that, The first time-domain reference signal and the first time-domain data signal are respectively subjected to transform-domain precoding to obtain two sets of frequency-domain signals, including: Phase-rotate the elements in the first time-domain reference signal to obtain the second time-domain reference signal; then perform transform-domain precoding on both the second time-domain reference signal and the first time-domain data signal to obtain the two sets of frequency-domain signals; or... The elements in the first time-domain data signal are phase-rotated to obtain the second time-domain data signal. The first time-domain reference signal and the second time-domain data signal are precoded in the transform domain to obtain the two sets of frequency-domain signals.

5. The method according to any one of claims 1-4, characterized in that, The step of interleaving and mapping the two sets of frequency domain signals to P frequency domain units includes: Map one of the two sets of frequency domain signals to the 2pth frequency domain unit among the P frequency domain units; Map the other set of frequency domain signals from the two sets of frequency domain signals to the (2p+1)th frequency domain unit in the P frequency domain units; p is greater than or equal to 0 and less than Integers, where This indicates rounding down to the nearest integer.

6. A communication method, characterized in that, The method includes: Receive signals sent by the transmitting end; The received signal is precoded in the transform domain to obtain two sets of frequency domain signals. One set of frequency domain signals includes the frequency domain signal corresponding to the first data signal sequence, and the other set of frequency domain signals includes the frequency domain signal corresponding to the first reference signal sequence. The two sets of frequency domain signals are interleaved and mapped in the frequency domain. In the time domain, the time units mapping the first data signal sequence and the time units mapping the first reference signal sequence do not overlap. In the time units mapping the first data signal sequence and the first reference signal sequence, the absolute value of the phase difference between the elements mapped in any two adjacent time units is θ. The time domain density of the first reference signal sequence is (1 / R). The time domain density of the first reference signal sequence is used to determine the number of time units mapping the first reference signal sequence. R is an integer greater than 2, and θ is not equal to 0. Perform channel equalization on the frequency domain signal corresponding to the first data signal sequence; Perform an inverse Fourier transform on the channel-equalized signal to obtain a first time-domain data signal. In the first time-domain data signal, the absolute value of the phase difference between any two adjacent elements is θ or 0. The first data signal sequence is obtained based on the first time-domain data signal.

7. The method according to claim 6, characterized in that, The two sets of frequency domain signals are interleaved and mapped in the frequency domain, including: one set of frequency domain signals is mapped to the 2p-th frequency domain unit in P frequency domain units, and the other set of frequency domain signals is mapped to the (2p+1)-th frequency domain unit in the P frequency domain units; wherein, P is greater than or equal to twice the sum of the length of the first reference signal sequence and the length of the first data signal sequence, and p is greater than or equal to 0 and less than 1 / 2. Integers, where This indicates rounding down to the nearest integer.

8. The method according to any one of claims 1-7, characterized in that, The value of θ is π / 2.

9. The method according to any one of claims 1-7, characterized in that, The value of R is 3, 4, or 5.

10. The method according to claim 9, characterized in that, When R equals 3 or 5, the first reference signal sequence is: - Binary phase shift keying sequence; When R equals 4, the first reference signal sequence is a binary phase shift keying sequence.

11. The method according to any one of claims 1-10, characterized in that, The ratio of the energy per resource unit corresponding to the first data signal sequence to the energy per resource unit corresponding to the first reference signal sequence is related to R.

12. The method according to any one of claims 1-11, characterized in that, The modulus of any two elements in the first reference signal sequence is the same, and the modulus of any two elements in the first data signal sequence is the same.

13. The method according to claim 12, characterized in that, The modulus of the elements in the first reference signal sequence is the same as the modulus of the elements in the first data signal sequence.

14. A communication device, characterized in that, Includes units or modules for performing the method as described in any one of claims 1 to 13.

15. A communication device, characterized in that, include: A processor coupled to a memory for storing programs or instructions that, when executed by the processor, cause the apparatus to perform the method as described in any one of claims 1 to 13.

16. A computer-readable storage medium having a computer program or instructions stored thereon, characterized in that, When the computer program or instructions are executed, they cause the computer to perform the method as described in any one of claims 1 to 13.

17. A computer program product, said computer program product comprising computer program code, characterized in that, When the computer program code is run on a computer, it causes the computer to perform the method of any one of claims 1 to 13.

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