A wireless power transmission system with high anti-deviation characteristics

Abstract

The present invention discloses a wireless power transmission system with high anti-offset characteristics, including a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2, a rectifier filter circuit and a load resistor connected in sequence. The transmitting unit P1 includes a transmitting coil T1 and an impedance unit Z01 connected in series, the transmitting unit P2 includes a transmitting coil T2 and an impedance unit Z02 connected in parallel, the receiving unit S1 includes a receiving coil R1 connected in series and an impedance unit Z03, and the receiving unit S2 includes a receiving coil R2 and an impedance unit Z04 connected in parallel. The transmitting coil T1 and the receiving coil R1 are connected by a mutual inductance M v Coupling, the transmitting coil T2 and the receiving coil R2 are connected by mutual inductance M i Coupling. Using mutual inductance M v With M i The characteristics of simultaneous increase or decrease under offset conditions greatly reduce the output fluctuation caused by the change in the relative position of the transmitting coil and the receiving coil, ensuring stable output under high offset conditions.

Description

Technical Field

[0001] The invention relates to a wireless power transmission system and belongs to the field of electric energy conversion. Background Art

[0002] Contactless power supply uses magnetic field coupling to achieve "wireless power supply", that is, a contactless transformer with completely separated primary and secondary sides is used to transmit electric energy through coupling of high-frequency magnetic field, so that there is no physical connection between the primary side (power supply side) and the secondary side (power consumption side) during the energy transfer process. Compared with traditional contact power supply, contactless power supply is convenient and safe to use, without sparks and electric shock hazards, dust accumulation and contact loss, mechanical wear and corresponding maintenance problems, can adapt to a variety of severe weather and environments, and is easy to realize automatic power supply, with broad application prospects.

[0003] However, the change in the relative position of the primary and secondary sides of the contactless transformer causes the transformer parameters to vary over a large range, resulting in fluctuations in system output and a significant decrease in transmission efficiency, limiting the promotion and application of WPT technology.

[0004] In order to improve the anti-deviation capability of wireless power transmission system, Mickel Budhia, John T. Boys, Grant A. Covic and Chang-Yu Huang, "Development of a Single-Sided Flux Magnetic Coupler for Electric Vehicle IPT Charging Systems" IEEE Transactions on Industrial Electronics, vol. 60, no. 1, January 2013 proposed to superimpose a third winding (referred to as Q winding) overlapping with the secondary winding between the two windings (referred to as DD winding) of the non-contact transformer secondary side, so as to reduce the sensitivity of the lateral misalignment of the secondary output power, and better solve the problem of "inductive blind spot" where "in and out magnetic fluxes are completely offset" when misaligned, which affects the power transmission capability of the transformer. However, this DDQ winding structure can only improve the output characteristics of the non-contact transformer under the condition of lateral misalignment. For the change of the vertical distance between the primary and secondary sides (i.e., the change of the air gap), the output characteristics of this "DDQ" winding structure still change greatly. Considering the uncertainty of the air gap size and misalignment between the primary and secondary sides of the contactless transformer in practical applications, further discussion and research are still needed.

[0005] Chinese Patent 201720241345.5, a voltage source and current source composite excitation non-contact conversion circuit utilizes the output characteristics of the non-contact converter under constant voltage source excitation is inversely proportional to the primary-secondary coupling coefficient (mutual inductance) of the non-contact transformer, and the output characteristics under constant current source excitation is proportional to the primary-secondary coupling coefficient (mutual inductance) of the non-contact transformer, compositely excites the voltage source and the current source, combines the output, and reduces the system output fluctuation caused by the change of mutual inductance, but its circuit structure is complex, requires a large number of passive components, and has a high cost. Summary of the invention

[0006] Purpose of the invention: In view of the above-mentioned prior art, a wireless power transmission system with high anti-offset characteristics is proposed to effectively improve the stability of the output characteristics under the condition of variable coupling coefficient.

[0007] Technical solution: A wireless power transmission system with high anti-offset characteristics, including a power source E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2, a rectifying and filtering circuit and a load resistor;

[0008] The transmitting unit P1 includes a transmitting coil T1 and an impedance unit Z01 connected in series;

[0009] The transmitting unit P2 includes a transmitting coil T2, a series impedance unit Z02a and a parallel impedance unit Z02b, wherein T2 is connected in series with Z02a and then connected in parallel with Z02b, or T2 is connected in parallel with Z02b and then connected in series with Z02a;

[0010] The receiving unit S1 comprises a receiving coil R1 and an impedance unit Z03 connected in series;

[0011] The receiving unit S2 comprises a receiving coil R2, a series impedance unit Z04a and a parallel impedance unit Z04b, R2 is connected in series with Z04a and then connected in parallel with Z04b, or R2 is connected in parallel with Z04b and then connected in series with Z04a;

[0012] The impedance units Z01, Z03, Z02a, and Z04a are wires or single inductors or single capacitors or a combination of multiple inductors and capacitors connected in series or in parallel;

[0013] The impedance unit Z02 and / or Z04 is a single inductor or a single capacitor or a combination of multiple inductors and capacitors connected in series or in parallel;

[0014] Wherein: the power source E is connected in series with the transmitting unit P1 and the transmitting unit P2 in sequence, the receiving unit S2, the receiving unit S1, the rectifier filter circuit and the load resistor are connected in series in sequence, and the transmitting coil T1 and the receiving coil R1 are connected in series via the mutual inductance M v The transmitting coil T2 and the receiving coil R2 are coupled by mutual inductance Mi coupling;

[0015] Or the power source E is connected in series with the transmitting unit P1 and the transmitting unit P2 in sequence, the receiving unit S1 is connected in parallel with the receiving unit S2 and then connected in series with the rectifier filter circuit and the load resistor in sequence, and the transmitting coil T1 and the receiving coil R2 are connected via the mutual inductance M v The transmitting coil T2 and the receiving coil R1 are coupled by mutual inductance M i coupling;

[0016] Or the transmitting unit P1 and the transmitting unit P2 are connected in parallel and powered by the power supply E, the receiving unit S2, the receiving unit S1, the rectifier filter circuit and the load resistor are connected in series in sequence, and the transmitting coil T1 and the receiving coil R2 are connected by the mutual inductance M v The transmitting coil T2 and the receiving coil R1 are coupled by mutual inductance M i coupling;

[0017] Or the transmitting unit P1 and the transmitting unit P2 are connected in parallel and powered by the power supply E, the receiving unit S1 and the receiving unit S2 are connected in parallel and then connected in series with the rectifier filter circuit and the load resistor in sequence, and the transmitting coil T1 and the receiving coil R1 are connected through the mutual inductance M v The transmitting coil T2 and the receiving coil R2 are coupled by mutual inductance M i coupling.

[0018] Furthermore, by setting the coil structures and phase positions of the transmitting coil T1, the transmitting coil T2, the receiving coil R1 and the receiving coil R2, there is no magnetic flux coupling or weak magnetic coupling between the transmitting coil T1 and the transmitting coil T2, between the transmitting coil T1 and the receiving coil R1, between the transmitting coil T2 and the receiving coil R1, and between the receiving coil R1 and the receiving coil R2 in the absence of offset.

[0019] Beneficial effect: The wireless power transmission system with high anti-offset characteristics proposed in the present invention has the main technical feature compared with the prior art. It adopts a dual transmitting coil and dual receiving coil structure, and utilizes the characteristics of the mutual inductance Mv and Mi increasing and decreasing together under offset conditions to construct an output voltage or output current that changes non-monotonic with the mutual inductance, so that when an offset occurs, the system can still have a stable output voltage or output current under constant input conditions, thereby improving the system's anti-offset capability. BRIEF DESCRIPTION OF THE DRAWINGS

[0020] Figure 1 It is a schematic diagram of the structure of a non-contact transformer;

[0021] Figure 2 Schematic diagram of the primary side structure of the non-contact transformer structure 1;

[0022] Figure 3 It is a schematic diagram of the second structure of the non-contact transformer;

[0023] Figure 4 It is the third schematic diagram of the non-contact transformer structure;

[0024] Figure 5 It is a schematic diagram of the structure of the non-contact transformer;

[0025] Figure 6 It is a schematic diagram of the structure of the non-contact transformer 5;

[0026] Figure 7 It is a schematic diagram of the structure of a contactless transformer VI;

[0027] Figure 8 Schematic diagram of the non-contact transformer structure 7;

[0028] Fig. 9 Schematic diagram of the non-contact transformer structure 8;

[0029] Fig.10 It is a schematic diagram of the structure of a non-contact transformer;

[0030] Fig.11 is a circuit diagram of Embodiment 1;

[0031] Fig.12 is the calculation result after the output current gain of the circuit in the first embodiment is normalized to per unit;

[0032] Fig.13 is a circuit diagram of Embodiment 2;

[0033] Fig.14 is the calculation result after the output voltage gain of the circuit shown in the second embodiment is normalized to unit;

[0034] Fig.15 is a circuit diagram of Embodiment 3;

[0035] Fig.16 is a circuit diagram of Embodiment 4;

[0036] Fig.17 is a circuit diagram of Embodiment 5;

[0037] Fig.18 is a circuit diagram of Embodiment 6;

[0038] Fig.19 is a circuit diagram of Embodiment 7;

[0039] Fig. 20 This is a schematic diagram of a circuit in which the coupled inductors are connected in series in the eighth embodiment;

[0040] Fig.21 This is a schematic diagram of a circuit in which the coupled inductor adopts an isolated structure according to the eighth embodiment;

[0041] Fig. 22 This is a schematic diagram of a circuit of an integrated coupled inductor and a contactless transformer winding according to Embodiment 8;

[0042] Fig.23 This is a schematic diagram of a circuit in which the coupled inductor is connected in series in the ninth embodiment;

[0043] Fig.24 This is a schematic diagram of a circuit of an integrated coupled inductor and a contactless transformer winding according to a ninth embodiment;

[0044] Fig.25 This is a schematic diagram of a circuit in which the coupled inductors are connected in a forward series manner according to the tenth embodiment;

[0045] Fig.26 This is a schematic diagram of a circuit in which a coupled inductor adopts an isolated structure according to Embodiment 10;

[0046] Fig. 27 This is a schematic diagram of a circuit of an integrated coupled inductor and a contactless transformer winding according to the tenth embodiment.

[0047] Fig.28 is a circuit diagram of Embodiment 11;

[0048] Fig.29 is a circuit diagram of Embodiment 12;

[0049] Fig.30 is a circuit diagram of Embodiment 13;

[0050] Fig.31 is a circuit diagram of Embodiment 14;

[0051] Fig.32 The coupling coefficient and mutual inductance measurement results of the non-contact transformer used in test example 1 and test example 2 at different air gaps;

[0052] Fig.33 This is the measurement result of the output current of test case 1 under different coupling coefficients and different load conditions;

[0053] Fig.34 This is the measurement result of the output voltage of test case 2 under different coupling coefficients and different load conditions;

[0054] Fig.35 It is a schematic diagram of the topological structure of the wireless power transmission system with high anti-deviation characteristics of the present invention. DETAILED DESCRIPTION

[0055] The present invention will be further explained below in conjunction with the accompanying drawings.

[0056] The transmitting unit P1, transmitting unit P2, receiving unit S1, and receiving unit S2 used in the wireless power transmission system with high anti-deviation characteristics of the present invention are implemented by non-contact transformers. Figure 1 Schematic diagram of the structure of a contactless transformer. The contactless transformer consists of a first transmitting coil 102 , a second transmitting coil 103 , a first receiving coil 202 , a second receiving coil 203 , a primary magnetic core 101 and a secondary magnetic core 201 . Figure 1 The purpose is to illustrate the coil structure of the contactless transformer. Without affecting the function, the magnetic core used can be transformed into other magnetic core shapes such as edge extension core, array core, cross core, etc.

[0057] Figures 1 to 9 Nine structures of non-contact transformers are given respectively. The arrows in the figure indicate the direction of the current flowing through the winding. Figures 3 to 10 Only the primary winding structure diagram of the non-contact transformer is given, corresponding to Figure 1 A contactless transformer structure can be obtained.

[0058] like Figure 1 As shown, the contactless transformer comprises, from top to bottom, a secondary magnetic core 201, a first receiving coil 202, a second receiving coil 203, an air gap, a first transmitting coil 102, a second transmitting coil 103, and a primary magnetic core 101. The first transmitting coil 102 and the second transmitting coil 103 are orthogonally overlapped and wound in the central area of ​​the primary magnetic core. The first receiving coil 202 and the second receiving coil 203 are orthogonally overlapped and wound in the central area of ​​the secondary magnetic core. The first transmitting coil 102 is composed of square coils 102A and 102B generating magnetic flux in opposite directions. The magnetic flux direction generated by 102A is perpendicular to the paper surface and outwards, and the magnetic flux direction generated by 102B is perpendicular to the paper surface and inwards, forming a closed state. The second transmitting coil 103 is composed of square coils 103A and 103B generating magnetic flux in opposite directions. The magnetic flux direction generated by 103A is perpendicular to the paper surface and outwards, and the magnetic flux direction generated by 103B is perpendicular to the paper surface and inwards, forming a closed state. Figure 2 As shown. The first receiving coil 202 is symmetrical with the first transmitting coil 102, and the second receiving coil 203 is symmetrical with the second transmitting coil 103. Then the first transmitting coil 102 is forward coupled with the first receiving coil 202, and the second transmitting coil 103 is forward coupled with the second receiving coil 203, and there are always two magnetic flux coupling channels.

[0059] like Figure 2As shown, the inflow and outflow magnetic fluxes generated by the first transmitting coil 102 coupled to the second transmitting coil 103 cancel each other, there is no magnetic flux coupling between 103 and 102, and the mutual inductance M1 is almost zero. Since the first receiving coil 202 is symmetrical with the first transmitting coil 102, and the second receiving coil 203 is symmetrical with the second transmitting coil 103, there is no magnetic flux coupling between the receiving coils 202 and 203, and the mutual inductance M2 is also zero; similarly, when the magnetic cores are facing each other, the inflow and outflow magnetic fluxes generated by the second transmitting coil 103 coupled to the first receiving coil 202 are completely canceled, and the inflow and outflow magnetic fluxes generated by the first transmitting coil 102 coupled to the second receiving coil 203 are completely canceled, and the mutual inductances M3 and M4 are both zero. Since the relative positions of the first transmitting coil 102 and the second transmitting coil 103, and the first receiving coil 202 and the second receiving coil 203 remain unchanged during the offset process, the mutual inductances M1 and M2 are always zero.

[0060] When the primary side is fixed and the secondary side of the contactless transformer is offset in the +Z direction, the primary and secondary cores are still facing each other, and the mutual inductances M1, M2, M3 and M4 are all zero; the first transmitting coil 102 is positively coupled with the first receiving coil 202, and the second transmitting coil 103 is positively coupled with the second receiving coil 203, but the magnetic resistance of the magnetic circuit corresponding to the coupling magnetic flux will increase due to the extension of the magnetic flux path, and the mutual inductance M i 、M v When the secondary side of the non-contact transformer is offset in the X direction, the mutual inductances M1 and M2 are zero, and the magnetic flux generated by the second transmitting coil 103 coupled to the receiving coils 202A and 202B cannot be completely offset. The magnetic flux generated by 202A and 202B coupled to the coil 103 has the same direction and the same effective area. Since 202A and 202B are connected in series in the forward direction, the effective magnetic flux of the second transmitting coil coupled to the first receiving coil 202 is zero, so that the mutual inductance M4 is zero; similarly, it can be found that M3 is also zero. When the X direction is offset, the magnetic resistance of the magnetic circuit corresponding to the magnetic flux coupled between the first transmitting coil 102 and the first receiving coil 202, and the second transmitting coil 103 and the second receiving coil 203 increases, and the area facing the winding decreases, resulting in the mutual inductance M4. i 、M v However, the magnetic flux coupled to the coil 203 has both inflow and outflow cancellation, which greatly reduces the effective magnetic conductive area, thereby making M i The downward trend is faster; e.g. Figure 1 As shown, the size of the coils 102 and 202 in the X direction is smaller than the size of the coils 103 and 203 in the X direction. When offset in the X direction, the area directly facing the first transmitting coil 102 and the first receiving coil 202 is reduced more than the area directly facing the second transmitting coil 103 and the second receiving coil 203. By reasonably setting the length-to-width ratio of the coils, the mutual inductance M can be i 、Mv decrease by approximately the same amount.

[0061] Similar to the flux coupling characteristics under X-direction misalignment, it can be found that under Y-direction misalignment, Figure 1 The non-contact transformer shown has mutual inductances M1, M2, M3 and M4 which are all zero, and mutual inductance M i 、M v decrease by approximately the same amount.

[0062] Figure 3 A second schematic diagram of the non-contact transformer structure used in the wireless power transmission system with high anti-bias characteristics of the present invention is given. The first transmitting coil 102 and the second transmitting coil 103 are orthogonally overlapped and wound in the central area of ​​the primary magnetic core, wherein the first transmitting coil 102 is composed of rectangular coils 102A and 102B that generate magnetic flux in opposite directions, the magnetic flux direction generated by 102A is perpendicular to the paper surface and outwards, and the magnetic flux direction generated by 102B is perpendicular to the paper surface and inwards, forming a closed shape, and the second transmitting coil 103 is composed of rectangular coils 103A and 103B that generate magnetic flux in opposite directions, the magnetic flux direction generated by 103A is perpendicular to the paper surface and outwards, and the magnetic flux direction generated by 103B is perpendicular to the paper surface and inwards, forming a closed shape. Coil structure and Figure 1 Similar, the difference is that the length-to-width ratio of the coil is different.

[0063] Figure 4 The following are three schematic diagrams of the contactless transformer structure used in the wireless power transmission system with high anti-deviation characteristics of the present invention. The first transmitting coil 102 is composed of rectangular coils 102A and 102B wound on two magnetic core side columns along the X direction and connected in series in a forward direction. The second transmitting coil 103 is composed of rectangular coils 103A and 103B wound on two magnetic core side columns along the Y direction and connected in series in a forward direction. The arrows in the figure indicate the direction of the current flowing through the winding. Figure 1 Similarly, when the displacement occurs in the X, Y, and Z directions, the mutual inductances M1, M2, M3, and M4 are all zero, and the mutual inductance M i 、M v All decreased.

[0064] Figure 5Four schematic diagrams of the non-contact transformer structure used in the wireless power transmission system with high anti-offset characteristics of the present invention are given. The first transmitting coil 102 is vertically wound around the magnetic core along the Y direction, and the second transmitting coil 103 is vertically wound around the magnetic core along the X direction. The arrows shown in the figure indicate the direction of the current flowing through the winding. Then the magnetic flux generated by the first transmitting coil 102 flows along the X direction path, parallel to the second transmitting coil 103, and the effective magnetic flux generated by the coil 102 coupled to the coil 103 is zero, and the mutual inductance M1 is zero. Due to the symmetry of the primary and secondary winding structures, the mutual inductance M3 is also zero. When the magnetic cores are facing each other, the direction of the magnetic flux generated by the first transmitting coil 102 is parallel to the second receiving coil 203, and the direction of the magnetic flux generated by the second transmitting coil 103 is parallel to the first receiving coil. The coupling magnetic flux is zero, resulting in zero mutual inductances M3 and M4. When the primary side is fixed and the secondary side of the contactless transformer is offset in the +Z direction, the primary and secondary cores are still facing each other, and the mutual inductances M1, M2, M3 and M4 are all zero; the first transmitting coil 102 is positively coupled with the first receiving coil 202, and the second transmitting coil 103 is positively coupled with the second receiving coil 203, but the magnetic resistance of the magnetic circuit corresponding to the coupling magnetic flux will increase due to the extension of the magnetic flux path, and the mutual inductance M i 、M v When the secondary side of the contactless transformer is offset in the X and Y directions, the mutual inductances M1 and M2 are zero, the magnetic flux generated by the first transmitting coil 102 flows along the X direction, parallel to the receiving coil 203, and the magnetic flux generated by the second transmitting coil 103 flows along the Y direction, parallel to the receiving coil 202, so that the mutual inductances M3 and M4 are zero. At the same time, the magnetic resistance of the magnetic circuit corresponding to the magnetic flux coupled between the first transmitting coil 102 and the first receiving coil 202, and the second transmitting coil 103 and the second receiving coil 203 increases, and the area facing the windings decreases, resulting in the mutual inductance M i 、M v All decreased.

[0065] Figure 6 A schematic diagram of the non-contact transformer structure used in the wireless power transmission system with high anti-bias characteristics of the present invention is given. The first transmitting coil 102 is composed of coils 102A and 102B symmetrically distributed on both sides of the magnetic core along the Y direction. The coils 102A and 102B are vertically wound around the magnetic core along the X direction. The second transmitting coil 103 is composed of coils 103A and 103B symmetrically distributed on both sides of the magnetic core along the X direction. The coils 103A and 103B are vertically wound around the magnetic core along the Y direction. The arrows shown in the figure indicate the direction of the current flowing through the winding. Its magnetic flux coupling characteristics are similar to Figure 4 Similarly, when the displacement occurs in the X, Y, and Z directions, the mutual inductances M1, M2, M3, and M4 are all zero, and the mutual inductance M i 、M v All decreased.

[0066] Figure 7Six schematic diagrams of the contactless transformer structure used in the wireless power transmission system with high anti-offset characteristics of the present invention are given. The first transmitting coil 102 is formed by two rectangular coils distributed on one diagonal of the rectangle connected in series, and the second transmitting coil 103 is formed by two rectangular coils distributed on the other diagonal of the rectangle connected in series. By reasonably designing the overlapping area of ​​coil 102 and coil 103, the magnetic flux in and out generated by the transmitting coil 103 coupled to the transmitting coil 102 can be completely offset, and the mutual inductance M1 is zero. Since the primary and secondary side structures are symmetrical, when the Z direction is misaligned, the mutual inductances M1, M2, M3 and M4 are all zero. However, when the displacement occurs in the X direction and the Y direction, the mutual inductances M1 and M2 are still zero, but the magnetic flux in and out generated by the receiving coil 202 coupled to the transmitting coil 103 cannot be offset, and the magnetic flux in and out generated by the receiving coil 203 coupled to the transmitting coil 102 cannot offset the mutual inductance, and both M3 and M4 are not zero, and increase with the increase of the displacement distance; at the same time, the magnetic resistance of the magnetic circuit corresponding to the magnetic flux coupled between the first transmitting coil 102 and the first receiving coil 202, and the second transmitting coil 103 and the second receiving coil 203 increases, and the area facing the windings decreases, resulting in the mutual inductance M1 and M2. i 、M v The magnetic core is not drawn in the figure.

[0067] Figure 8 The present invention provides a schematic diagram of the contactless transformer structure used in the wireless power transmission system with high anti-offset characteristics. The arrows in the figure indicate the direction of the current in the winding. The first transmitting coil 102 is composed of rectangular coils 102A and 102B that generate magnetic flux in opposite directions. The direction of the magnetic flux generated by 102A is perpendicular to the paper surface and inward, and the direction of the magnetic flux generated by 102B is perpendicular to the paper surface and outward, forming a closed state. The second transmitting coil 103 is composed of rectangular coils 103A and 103B that generate the same magnetic flux direction. The directions of the magnetic flux generated by 103A and 103B are both perpendicular to the paper surface and outward. The magnetic flux generated by the transmitting coil 102 coupled to the transmitting coil 103A and 103B is completely offset in and out, and the mutual inductance M1 is zero. Since the primary and secondary side structures are symmetrical, when the Z direction is misaligned, the mutual inductances M1, M2, M3 and M4 are all zero. When the X-direction offset occurs, the magnetic flux in and out generated by the first transmitting coil 102 coupled to the receiving coils 203A and 203B are completely offset, and the effective magnetic flux of the first transmitting coil coupled to the receiving coil 203 is zero, so that the mutual inductance M3 is zero; similarly, due to the symmetry of the primary and secondary structures, it can be found that M4 is also zero; at the same time, the magnetic resistance of the magnetic circuit corresponding to the magnetic flux coupled between the first transmitting coil 102 and the first receiving coil 202, and the second transmitting coil 103 and the second receiving coil 203 increases, and the area of ​​the windings facing each other decreases, resulting in the mutual inductance M i 、M v When the Y direction offset occurs, the mutual inductance M i 、M vAt the same time, by reasonably designing the overlapping area between coil 102 (202) and coils 103A (203A) and 103B (203B), the magnetic flux in and out generated by coil 103 coupled to coil 102 can cancel each other out, and the mutual inductances M3 and M4 are zero.

[0068] Fig. 9 The following is a schematic diagram of the contactless transformer structure used in the wireless power transmission system with high anti-offset characteristics of the present invention. The arrow in the figure indicates the direction of the current in the winding. The first transmitting coil 102 is composed of rectangular coils 102A and 102B that generate magnetic flux in opposite directions. The direction of the magnetic flux generated by 102A is perpendicular to the paper surface and inward, and the direction of the magnetic flux generated by 102B is perpendicular to the paper surface and outward, forming a closed state. The second transmitting coil 103 is stacked and wound at the center of the first transmitting coil 102. The magnetic flux generated by the transmitting coil 102 coupled to the transmitting coil 103 is completely offset in and out, and the mutual inductance M1 is zero. Since the primary and secondary side structures are symmetrical, when the Z direction is misaligned, the mutual inductances M1, M2, M3 and M4 are all zero. When the Y direction offset occurs, the left half of the magnetic flux generated by the transmitting coil 102 coupled to the receiving coil 203 enters and the right half exits, and the total effective magnetic flux is zero, so that the mutual inductance M3 is zero. Similarly, due to the symmetry of the primary and secondary structures, it can be found that M4 is also zero. At the same time, the magnetic resistance of the magnetic circuit corresponding to the magnetic flux coupled between the first transmitting coil 102 and the first receiving coil 202, and the second transmitting coil 103 and the second receiving coil 203 increases, and the area of ​​the windings facing each other decreases, resulting in the mutual inductance M i 、M v When the X direction offset occurs, the mutual inductance M i 、M v However, the magnetic flux in and out generated by the transmitting coil 102 (103) coupled to the receiving coil 203 (202) cannot be offset, and the mutual inductances M3 and M4 gradually increase.

[0069] Fig.10A schematic diagram of the non-contact transformer structure used in the wireless power transmission system with high anti-offset characteristics of the present invention is given. The arrow in the figure indicates the direction of the current in the winding. The first transmitting coil 102 is stacked on the second transmitting coil 103, and the two coils partially overlap. By designing the overlapping area of ​​the two coils, the magnetic flux generated by the transmitting coil 102 coupled to the transmitting coil 103 can be completely offset in both inflow and outflow, and the mutual inductance M1 is zero. Since the primary and secondary side structures are symmetrical, when the Z direction is misaligned, the mutual inductances M1, M2, M3 and M4 are all zero. When the Y direction is offset, the magnetic flux generated by the transmitting coil 102 coupled to the receiving coil 203 is either inflow or outflow, the total effective magnetic flux is zero, and the mutual inductance M3 is zero. Similarly, due to the symmetry of the primary and secondary side structures, M4 is also zero; at the same time, the magnetic resistance of the magnetic circuit corresponding to the magnetic flux coupled between the first transmitting coil 102 and the first receiving coil 202, and the second transmitting coil 103 and the second receiving coil 203 increases, and the area facing the winding decreases, resulting in the mutual inductance M i 、M v When the X direction offset occurs, the mutual inductance M i 、M v However, the magnetic flux in and out generated by the transmitting coil 102 (103) coupled to the receiving coil 203 (202) cannot be offset, and the mutual inductances M3 and M4 gradually increase.

[0070] based on Figure 1 The non-contact transformer structure shown can further analyze the working principle of the technical solution of the present invention. It is worth noting that the wireless power transmission system with high anti-drift characteristics of the present invention requires that during the drift process, the values ​​of the mutual inductances M1, M2, M3 and M4 are very small, close to zero or equal to zero, and only the mutual inductance M i 、M v , and as the offset distance increases, M v 、M i The corresponding coupling coefficient k v , k i Approximately satisfy the linear relationship change, that is, k v ≈ak i + b, a and b are constants. In the following embodiments, Figure 1 The contactless transformer structures and circuit topologies shown can be freely combined.

[0071] The wireless power transmission system consists of a DC voltage source, a high-frequency inverter, a resonant conversion unit, a rectifier filter circuit R and a load R connected in sequence. L. In order to highlight the design focus of the present invention, the AC / AC resonant conversion unit is taken as the research object of the present invention. In order to improve the efficiency of the contactless converter, the converter is generally designed to work near the resonant frequency point, and the resonant inductor current is approximately sinusoidal. Then the fundamental wave approximation analysis method can be used to replace all variables in the resonant network with their fundamental wave components. The high-frequency inverter output is equivalent to an AC voltage source When the rectifier bridge is continuously turned on, the voltage and current at the midpoint of its bridge arm are always in phase, and the rectifier filter circuit is equivalent to a load resistor R E , satisfying R E =8 / π 2 R L , R E is the equivalent load resistance, R L is the load resistance. There are many optional circuits for high-frequency inverters, including push-pull, half-bridge, full-bridge circuits, etc. There are also many optional circuits for the rectifier filter circuit R, including bridge rectification, full-wave rectification, half-wave rectification, current doubler rectification, voltage doubler rectification, etc.

[0072] Embodiment 1:

[0073] Fig.11 The circuit structure diagram of the first embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r , capacitor C r The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv ; The transmitting unit P2 includes a transmitting coil L connected in parallel pi and resonant capacitor C ppi The receiving unit S1 includes a receiving coil L connected in series si and resonant capacitor C si ; The receiving unit S2 includes a receiving coil L sv , resonant capacitor C spv and resonant inductor L rs , where L sv With C spv After connecting in parallel with L rs The power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2 in sequence, and the receiving unit S2 is connected in parallel with the receiving unit S1 to provide a load resistor R E Power supply, transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L piand receiving coil L si Through mutual inductance M i coupling.

[0074] The resonant element parameters satisfy:

[0075]

[0076] Where ω0 is the resonant frequency. r With C r Resonance, flowing through the transmitting coil L pv Current Constant. According to the basic circuit theory, we can find that the current flowing through the transmitting coil L at the resonant frequency ω0 pv , transmitting coil L pi , receiving coil L si and receiving coil L sv Current and They are:

[0077]

[0078] Furthermore, the output current gain and input impedance are:

[0079]

[0080]

[0081] in, is the output current. k v , k i Mutual inductance M v 、M i Under full compensation conditions, the output current gain of the first embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Figure 1 The contactless transformer structure given in FIG. 1 shows that when the secondary side of the contactless transformer is offset relative to the primary side, the mutual inductance M v 、M i The change trend is the same. Taking the displacement along the +Z direction as an example, M v 、M i Both decrease, correspondingly M v / L sv decreases, while L pi / M i will increase, by reasonably designing the transformer parameters, The increase in compensation ω0M v If the reduction amount is reduced, constant current output can be achieved within a certain offset condition, thereby improving the anti-offset characteristics of the wireless power transmission system.

[0082] Let kv =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the minimum point of the output current gain and the corresponding coupling coefficient k can be obtained. e for:

[0083]

[0084]

[0085] G iv (k) represents the output current gain when the coupling coefficient is k, G iv (k e ) is k=k e The output current gain when , further, the output current gain is calibrated with the minimum value,

[0086]

[0087] G iv *(k) represents the output current gain after standardization when the coupling coefficient is k. Assuming a=1, b=0, taking different ke values, we can draw a curve of the output current gain after standardization as the coupling coefficient changes, as shown in Fig.12 As shown in Figure 2, it can be found that the output current gain after standardization changes non-monotonicly with the coupling coefficient, and changes slowly near the extreme point. In a given coupling coefficient interval [k min , k max ] to achieve minimal output current fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0088] When the coupling coefficient k is in the interval [k min , k max ] changes within , and k e ∈[k min , k max ], define the output current fluctuation G ivmax is the maximum output current gain, G ivmin is the minimum output current gain, then according to Fig.12 It can be seen that the output current fluctuation ξ is

[0089]

[0090] G iv (k max ) is expressed as k = k max The output current gain, G iv (k min ) is expressed as k = k minThe output current gain when the resonant element is 0.0001mm / s. The parameters of the resonant element in the first embodiment of the present invention satisfy When the effective coupling coefficient is in the range [k min , k max ] to achieve the minimum output current fluctuation. The proof process is as follows:

[0091] When the coupling coefficient is k, the output current gain can be expressed as

[0092]

[0093]

[0094] ∵max{G iv (k max ), G iv (k max )}≥G iv (k max ), max{G iv (k max ), G iv (k min )}≥G iv (k min )

[0095]

[0096] The following proves that the conditions for obtaining the equality sign are simultaneously met, when G iv (k max )=G iv (k min )

[0097]

[0098] ∵k max >k min ∴

[0099] Embodiment 2:

[0100] Fig.13 The circuit structure diagram of the second embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r1 , capacitor C r 、Inductance L r2 The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv; The transmitting unit P2 includes a transmitting coil L pi , resonant capacitor C ppi , C psi and resonant inductor L sr , where the transmitting coil L pi With capacitor C psi After connecting in series with capacitor C ppi In parallel, and then with the resonant inductor L sr The receiving unit S1 includes a receiving coil L connected in series. sv and resonant capacitor C sv ; The receiving unit S2 includes a receiving coil L si , resonant capacitor C ssi , C spi and resonant inductor L ssi , where L si With C ssi After connecting in series with C spi Connect in parallel with L ssi The transmitting unit P1 and the transmitting unit P2 are connected in parallel and powered by the power supply E. The receiving unit S2 and the receiving unit S1 are connected in parallel and powered by the load resistor R. E Power supply, transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0101] The resonant element parameters satisfy:

[0102]

[0103] Where ω0 is the resonant frequency. r1 With C r Resonance, current Constant. According to the basic circuit theory, we can find that the current flowing through the transmitting coil L at the resonant frequency ω0 pv , transmitting coil L pi , receiving coil L si and receiving coil L sv Current and They are:

[0104]

[0105] Furthermore, the output voltage gain and input impedance are:

[0106]

[0107]

[0108] in, is the output voltage. k v , k i Mutual inductance M v 、M i The corresponding coupling coefficient. Under the full compensation condition, the output voltage gain of the second embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k i =ak v +b=ak+b, a and b are constants, k is the coupling coefficient, and the maximum point of the output voltage gain and the corresponding coupling coefficient k can be obtained. e for:

[0109]

[0110]

[0111] G vv (k e ) is k=k e The output voltage gain at this time, further, the output voltage gain is calibrated with the maximum value,

[0112]

[0113] G vv * (k) represents the output voltage gain after scaling when the coupling coefficient is k. Assuming a=1, b=0, taking different k e The output voltage gain after standardization can be plotted as the coupling coefficient changes. Fig.14 As shown in Figure 2, it can be found that the output voltage gain after standardization changes non-monotonicly with the coupling coefficient, and changes slowly near the extreme point. e The value can be given in the coupling coefficient interval [k min , k max ] to achieve minimal output voltage fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0114] Different from the first embodiment, the second embodiment of the present invention can achieve constant voltage output within a wider range of coupling coefficient and load variation.

[0115] When the coupling coefficient k is in the interval [k min , k max ] changes within , and k e ∈[k min , k max ], the output voltage fluctuation is defined as Gvvmax is the maximum output current gain, G vvmin is the minimum output current gain, then according to Fig.14 It can be seen that the output voltage fluctuation ξ is

[0116]

[0117] G vv (k max ) is expressed as k = k max The output voltage gain, G vv (k min ) is expressed as k = k min The output voltage gain when the resonant element is . The parameters of the resonant element in the second embodiment of the present invention satisfy When the effective coupling coefficient is in the range [k min , k max ] to achieve the minimum output voltage fluctuation. The proof process is as follows:

[0118] When the coupling coefficient is k, the output voltage gain can be expressed as

[0119]

[0120] make

[0121]

[0122] ∵H(k max )≤max(H(k max ), H(k min )), H(k min )≤max(H(k max ), H(k min ))

[0123]

[0124] G vv (k) represents the output voltage gain when the coupling coefficient is k;

[0125] The following proves that the conditions for obtaining the equality sign are simultaneously met, when H(k max )=H(k min )

[0126]

[0127] Where H(x) represents the value of H when the coupling coefficient k is x.

[0128] Embodiment three:

[0129] Fig.15The circuit structure diagram of the third embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r , resistor C r The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv ; The transmitting unit P2 includes a transmitting coil L connected in parallel pi and resonant capacitor C ppi The receiving unit S1 includes a receiving coil L connected in series sv and resonant capacitor C sv The receiving unit S2 includes a receiving coil L connected in parallel si and resonant capacitor C spi The power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2, and the receiving unit S2, the receiving unit S1 and the load resistor R E Connect in series, the transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0130] The resonant element parameters satisfy:

[0131]

[0132] Where ω0 is the resonant frequency. r With C r Resonance, flowing through the transmitting coil L pv Current When operating at the resonant frequency ω0, the current flowing through the transmitting coil L pv , transmitting coil L pi , receiving coil L si and receiving coil L sv Current and They are:

[0133]

[0134] The output voltage gain and input impedance are:

[0135]

[0136]

[0137] in, is the output voltage. k v , k i Mutual inductance M v 、M i Under the full compensation condition, the output voltage gain of the third embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. v 、M i The corresponding coupling coefficient k v , k i Indicates that k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the minimum point of the output voltage gain and the corresponding coupling coefficient k can be obtained. e for:

[0138]

[0139]

[0140] G vv (k) represents the output voltage gain when the coupling coefficient is k, G vv (k e ) is k=k e The output voltage gain at this time, further, the output voltage gain is calibrated with the minimum value,

[0141]

[0142] G vv *(k) represents the output current gain after scaling when the coupling coefficient is k, and its expression is the same as that of the first embodiment of the present invention, and has similar external characteristics. In a given coupling coefficient interval [k min , k max ], to achieve the minimum output voltage fluctuation and improve the anti-deviation characteristics of the wireless power transmission system. Embodiment 3 of the present invention requires that the transmitting coil L pv , transmitting coil L pi , receiving coil L si and receiving coil L sv The self-sensitivity value satisfies

[0143]

[0144] Embodiment 4:

[0145] Fig.16The circuit structure diagram of the fourth embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r , capacitor C r The LC resonant network is composed of the transmitting unit P1 including the transmitting coil L pv ; The transmitting unit P2 includes a transmitting coil L pi , resonant capacitor C psi and C ppi , where the transmitting coil L pi With capacitor C psi After connecting in series with capacitor C ppi Connected in parallel; the receiving unit S1 includes a receiving coil L sv ; The receiving unit S2 includes a receiving coil L si , resonant capacitor C spi and C ssi , where the receiving coil L si With capacitor C ssi After connecting in series with capacitor C spi The power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2, and the receiving unit S2, the receiving unit S1 and the load resistor R E Connect in series, the transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0146] The resonant element parameters satisfy:

[0147]

[0148] Where ω0 is the resonant frequency. r With C r Resonance, flowing through the transmitting coil L pv Current When operating at the resonant frequency ω0, the current flowing through the transmitting coil L pv , transmitting coil L pi , receiving coil L si and receiving coil L sv Current and They are:

[0149]

[0150] The output voltage gain and input impedance are:

[0151]

[0152]

[0153] in, is the output voltage. k v , k i Mutual inductance M v 、M i Under the full compensation condition, the output voltage gain of the fourth embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the minimum point of the output voltage gain and the corresponding coupling coefficient k can be obtained. e for:

[0154]

[0155]

[0156] G vv (k) represents the output current gain when the coupling coefficient is k, G vv (k e ) is k=k e The output voltage gain is different from that in the third embodiment. The transmitting coil L in the fourth embodiment of the present invention is pv , transmitting coil L pi , receiving coil L si and receiving coil L sv The self-inductance value is required to meet:

[0157] λ p =L pv / L pi ,λ s =L sv / L si (33)

[0158] Furthermore, the output voltage gain is normalized to the minimum value, and we have

[0159]

[0160] G vv *(k) represents the output voltage gain after per-unit when the coupling coefficient is k. Its expression is the same as the output current gain expression after per-unit in the first embodiment of the present invention, and has similar external characteristics. It can be found that the output voltage gain after per-unit changes non-monotonically with the coupling coefficient, and changes slowly near the extreme point. Therefore, by designing In a given coupling coefficient interval [k min , k max ] to achieve minimal output voltage fluctuation, improve the anti-offset characteristics of the wireless power transmission system, and achieve constant voltage output within a wider range of coupling coefficient changes and load changes.

[0161] Embodiment five:

[0162] Fig.17 The circuit structure diagram of the fifth embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r , capacitor C r The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv ; The transmitting unit P2 includes a transmitting coil L pi , resonant capacitor C psi and C ppi , where the transmitting coil L pi With capacitor C psi After connecting in series with capacitor C ppi The receiving unit S1 includes a receiving coil L connected in series. sv and resonant capacitor C sv ; The receiving unit S2 includes a receiving coil L si , resonant capacitor C spi and C ssi , where the receiving coil L si With capacitor C ssi After connecting in series with capacitor C spi The power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2, and the receiving unit S2, the receiving unit S1 and the load resistor R E Connect in series, the transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0163] The resonant element parameters satisfy:

[0164]

[0165] Where ω0 is the resonant frequency. r With C r Resonance, flowing through the transmitting coil L pv Current When operating at the resonant frequency ω0, the current flowing through the transmitting coil L pv , transmitting coil L pi , receiving coil L si and receiving coil L sv Current and They are:

[0166]

[0167] The output voltage gain and input impedance are:

[0168]

[0169]

[0170] in, is the output voltage, k v , k i Mutual inductance M v 、M i Under the full compensation condition, the output voltage gain of the fifth embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the minimum point of the output voltage gain and the corresponding coupling coefficient k can be obtained. e for:

[0171]

[0172] G vv (k) represents the output voltage gain when the coupling coefficient is k, G vv (k e ) is k=k e The output voltage gain at this time, further, the output voltage gain is calibrated with the minimum value,

[0173]

[0174] G vv*(k) represents the output voltage gain after per-unit when the coupling coefficient is k. Its expression is the same as the output current gain expression after per-unit in the first embodiment of the present invention, and has similar external characteristics. It can be found that the output voltage gain after per-unit changes non-monotonically with the coupling coefficient, and changes slowly near the extreme point. Through reasonable design In a given coupling coefficient interval [k min , k max ] to achieve minimal output voltage fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0175] Different from the fourth and third embodiments of the present invention, the compensation capacitor C in the fifth embodiment psi , C ssi This provides design freedom to minimize output voltage fluctuations, that is, the compensation capacitor C can be adjusted for any non-contact transformer parameters. psi , C ssi to satisfy the value of This allows constant voltage output to be achieved over a wider range of coupling coefficients and load variations.

[0176] Embodiment six:

[0177] Fig.18 The circuit structure diagram of the sixth embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r , capacitor C r The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv ; The transmitting unit P2 includes a transmitting coil L pi and resonant capacitor C ppi , C psi , L pi With C psi After connecting in series with C ppi The receiving unit S1 includes a receiving coil L connected in series. si and resonant capacitor C si ; The receiving unit S2 includes a receiving coil L sv , resonant capacitor C spv , C spv and resonant inductor L rs , where L sv With C ssv After connecting in series with C spv Connect in parallel with L rsThe power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2 in sequence, and the receiving unit S2 is connected in parallel with the receiving unit S1 to provide a load resistor R E Power supply, transmitting coil L pv and receiving coil L sv Through mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0178] The resonant element parameters satisfy:

[0179]

[0180] Where ω0 is the resonant frequency. r With C r Resonance, flowing through the transmitting coil L pv Current Constant. According to the basic circuit theory, we can find that the current flowing through the transmitting coil L at the resonant frequency ω0 pv , transmitting coil L pi , receiving coil L si and receiving coil L sv Current and They are:

[0181]

[0182] in, Furthermore, the output current gain and input impedance are:

[0183]

[0184]

[0185] in, is the output current, k v , k i Mutual inductance M v 、M i Under the full compensation condition, the output current gain of the first embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the minimum point of the output current gain and the corresponding coupling coefficient k can be obtained. e for:

[0186]

[0187] Giv (k) represents the output current gain when the coupling coefficient is k, G iv (k e ) is k=k e The output current gain when , further, the output current gain is calibrated with the minimum value,

[0188]

[0189] G iv *(k) represents the output current gain after standardization when the coupling coefficient is k. The output current gain after standardization is the same as that in the first embodiment of the present invention. In a given coupling coefficient interval [k min , k max ] to achieve minimal output current fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0190] Different from the first embodiment of the present invention, the compensation capacitor C in the sixth embodiment psi , C ssi This provides design freedom to achieve minimum output current fluctuation, that is, the compensation capacitor C can be adjusted for any non-contact transformer parameters. psi , C ssv to satisfy the value of This allows constant current output to be achieved within a wider range of coupling coefficient and load variations.

[0191] Embodiment seven:

[0192] Fig.19 The circuit structure diagram of the seventh embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r1 , capacitor C r 、Inductance L r2 The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv ; The transmitting unit P2 includes a transmitting coil L pi , resonant capacitor C ppi and resonant inductor L sr , where the transmitting coil L pi With capacitor C ppi In parallel, and then with the resonant inductor L sr The receiving unit S1 includes a receiving coil L connected in series. sv and resonant capacitor C sv; The receiving unit S2 includes a receiving coil L si , resonant capacitor C spi and resonant inductor L ssi , where L si With C spi Connect in parallel with L ssi The transmitting unit P1 and the transmitting unit P2 are connected in parallel and powered by the power supply E. The receiving unit S2 and the receiving unit S1 are connected in parallel and powered by the load resistor R. E Power supply, transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi With receiving coil L si Through mutual inductance M i coupling.

[0193] The resonant element parameters satisfy:

[0194]

[0195] Where ω0 is the resonant frequency. r1 With C r Resonance, current Constant. According to the basic circuit theory, we can find that the current flowing through the transmitting coil L at the resonant frequency ω0 pv , transmitting coil L pi , receiving coil L si and receiving coil L sv Current and They are:

[0196]

[0197] Furthermore, the output voltage gain and input impedance are:

[0198]

[0199]

[0200] in, is the output voltage, k v , k i Mutual inductance M v 、M i The corresponding coupling coefficient. Under the full compensation condition, the output voltage gain of the seventh embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k i =ak v +b=ak+b, a and b are constants, k is the coupling coefficient, and the maximum point of the output voltage gain and the corresponding coupling coefficient k can be obtained. e for:

[0201]

[0202] G vv (k) represents the output voltage gain when the coupling coefficient is k, G iv (k e ) is k=k e The output voltage gain at this time, further, the output voltage gain is calibrated with the maximum value,

[0203]

[0204] G vv *(k) represents the output voltage gain after per-unit when the coupling coefficient is k, and its expression is the same as the output voltage gain expression after per-unit in the second embodiment of the present invention. In a given coupling coefficient interval [k min , k max ] to achieve minimal output voltage fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0205] Different from the second embodiment, when a≈1, the seventh embodiment of the present invention requires the non-contact transformer winding self-inductance L pv , L pi , L si and L sv Approximate satisfaction

[0206]

[0207] It can be in the effective coupling coefficient range [k min , k max ] to achieve minimal output voltage fluctuation.

[0208] Embodiment eight:

[0209] Fig. 20 , Fig.21 The circuit structure diagram of the eighth embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r1 , capacitor C r The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv; The transmitting unit P2 includes a coupled inductor T1 and a transmitting coil L connected in series pi , resonant capacitor C psi The receiving unit S1 includes a coupled inductor T2 and a receiving coil L connected in series. si , resonant capacitor C ssi The receiving unit S2 includes a receiving coil L connected in series sv and resonant capacitor C sv The power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2, and the receiving unit S1 and the receiving unit S2 are connected in series with the load resistor R E Connect in series, the transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0210] The coupled inductor T1 includes self-inductance L1, L2 and mutual inductance M 12 , the coupled inductor T2 includes self-inductance L3, L4 and mutual inductance M 34 ,like Fig. 20 As shown, L1 and L2 are connected in series in a forward direction, and L1 and the transmitting coil L pv Connect in series, L2 and transmitting coil L pi Series connection; L3 and L4 are connected in series in the forward direction, L3 and the receiving coil L sv Series connection, L4 and receiving coil L si Connect in series. Fig.21 As shown, the coupled inductors T1 and T2 can also be isolated structures, L1 and L2 have no electrical connection, and are connected through mutual inductance M 12 Realize magnetic flux coupling; Similarly, L3 and L4 have no electrical connection, through mutual inductance M 34 Achieve magnetic flux coupling.

[0211] Fig. 20 , Fig.21 The parameters of the resonant components in the circuit shown satisfy:

[0212]

[0213] Where ω0 is the resonant frequency. r1 With C r Resonance, current Constant. According to the basic circuit theory, the output voltage gain at the resonant frequency ω0 can be obtained as:

[0214]

[0215]

[0216] in, is the output voltage, k v , k i Mutual inductance M v 、M i Under the full compensation condition, the output voltage gain of the eighth embodiment of the present invention has nothing to do with the load, the input impedance is always pure resistance, and has similar external characteristics to the fifth embodiment.

[0217] Let k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the minimum point of the output voltage gain and the corresponding coupling coefficient k can be obtained. e for:

[0218]

[0219] G vv (k) represents the output voltage gain when the coupling coefficient is k, G vv (k e ) is k=k e The output voltage gain at this time, further, the output voltage gain is calibrated with the minimum value,

[0220]

[0221] G vv *(k) represents the output voltage gain after per-unit when the coupling coefficient is k, and its expression is the same as the output current gain expression after per-unit in the first embodiment of the present invention. In a given coupling coefficient interval [k min , k max ] to achieve minimal output voltage fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0222] In addition, winding L1 and L pv , winding L2 and L pi , winding L3 and L sv , winding L4 and L si Integration, realize winding sharing, reduce coil volume and weight, such as Fig. 22 It is worth noting that the transmitting coil L pv With L pi , receiving coil L sv With L si There is flux coupling, the same-name ends are represented by “·”, and the corresponding mutual inductances are M 12 、M 34 .

[0223] Embodiment nine:

[0224] Fig.23 , Fig.24 The circuit structure diagram of the ninth embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E . Power source E is an AC voltage source The transmitting unit P1 includes a transmitting coil L connected in series pv and resonant capacitor C pv ; The transmitting unit P2 includes a coupled inductor T1 and a transmitting coil L connected in series pi , resonant capacitor C psi The receiving unit S1 includes a coupled inductor T2 and a receiving coil L connected in series. si , resonant capacitor C ssi The receiving unit S2 includes a receiving coil L connected in series sv and resonant capacitor C spv The power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2, and the receiving unit S1 and the receiving unit S2 are connected in series with the load resistor R E Connect in series, the transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0225] The coupled inductor T1 includes self-inductance L1, L2 and mutual inductance M 12 , the coupled inductor T2 includes self-inductance L3, L4 and mutual inductance M 34 ,like Fig.23 As shown, L1 and L2 are connected in series in a forward direction, and L1 and the transmitting coil L pv Connect in series, L2 and transmitting coil L pi Connect in series. The parameters of the resonant components in the circuit satisfy:

[0226]

[0227] Where ω0 is the resonant frequency. According to the basic circuit theory, the output current gain and input impedance at the resonant frequency ω0 can be obtained as:

[0228]

[0229]

[0230] in, is the output current, k v , k iMutual inductance M v 、M i Under the full compensation condition, the output current gain of the ninth embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the maximum point of the output current gain and the corresponding coupling coefficient k can be obtained. e for:

[0231]

[0232] G iv (k) represents the output current gain when the coupling coefficient is k, G iv (k e ) is k=k e The output current gain at this time, further, the output current gain is calibrated with the maximum value,

[0233]

[0234] G iv *(k) represents the output current gain after standardization when the coupling coefficient is k, and its expression is the same as the output voltage gain expression after standardization in the second embodiment of the present invention. In a given coupling coefficient interval [k min , k max ] to achieve minimal output current fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0235] In addition, winding L1 and L pv , winding L2 and L pi , winding L3 and L sv , winding L4 and L si Integration, realize winding sharing, reduce coil volume and weight, such as Fig.24 It is worth noting that the transmitting coil L pv With L pi , receiving coil L sv With L si There is flux coupling, the same-name ends are represented by “·”, and the corresponding mutual inductances are M 12 、M 34 .

[0236] Embodiment ten:

[0237] Figure 25 to Figure 27The circuit structure diagram of the tenth embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E The power source E includes an AC voltage source and inductor L r , capacitor C r The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv ; The transmitting unit P2 includes a coupled inductor T1 and a transmitting coil L connected in series pi , resonant capacitor C psi The receiving unit S1 includes a coupled inductor T2 and a receiving coil L connected in series. si , resonant capacitor C ssi ; The receiving unit S2 includes a receiving coil L sv , resonant capacitor C sv , C q With the resonant inductor L q , where L sv With C sv After connecting in series with C q Connect in parallel with L q The power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2, and the receiving unit S2, the receiving unit S1 and the load resistor R E Connect in series, the transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0238] The coupled inductor T1 includes self-inductance L1, L2 and mutual inductance M 12 , the coupled inductor T2 includes self-inductance L3, L4 and mutual inductance M 34 ,like Fig.25 As shown, L1 and L2 are connected in series in a forward direction, and L1 and the transmitting coil L pv Connect in series, L2 and transmitting coil L pi Series connection; L3 and L4 are connected in series in the forward direction, L3 and the receiving coil L sv Series connection, L4 and receiving coil L si Connect in series. Fig.26 As shown, the coupled inductors T1 and T2 can also be isolated structures, L1 and L2 have no electrical connection, and are connected through mutual inductance M 12 Realize magnetic flux coupling; Similarly, L3 and L4 have no electrical connection, through mutual inductance M 34Realize magnetic flux coupling. The parameters of the resonant components in the circuit meet the following requirements:

[0239]

[0240] Where ω0 is the resonant frequency. r With C r Resonance, current Constant. According to the basic circuit theory, the output current gain at the resonant frequency ω0 can be obtained as:

[0241]

[0242]

[0243] in, is the output current, k v , k i Mutual inductance M v 、M i Under the full compensation condition, the output current gain of the tenth embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance.

[0244] Let k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the minimum point of the output current gain and the corresponding coupling coefficient k can be obtained. e for:

[0245]

[0246] G iv (k) represents the output current gain when the coupling coefficient is k, G iv (k e ) is k=k e The output current gain when the output voltage gain is further calibrated with the minimum value,

[0247]

[0248] G iv *(k) represents the output current gain after per-unit when the coupling coefficient is k, and its expression is the same as the output current gain expression after per-unit in the first embodiment of the present invention. In a given coupling coefficient interval [k min , k max ] to achieve minimal output current fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0249] Embodiment eleven:

[0250] Fig.28 The circuit structure diagram of the eleventh embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and a load resistor R E . Power source E is an AC current source It can also be obtained by converting an AC voltage source plus an LC resonant network; the transmitting unit P1 includes a transmitting coil L connected in series pv and resonant capacitor C pv The transmitting unit P2 includes a coupled inductor T1, a resonant capacitor C1 and a transmitting coil L connected in series. pi , resonant capacitor C psi The receiving unit S1 includes a receiving coil L connected in series sv and resonant capacitor C sv The receiving unit S2 includes a coupled inductor T2, a resonant capacitor C2 and a receiving coil L connected in series. si , resonant capacitor C ssi The transmitting unit P1 is connected in parallel with the transmitting unit P2 and is powered by the power supply E. The receiving unit S2 is connected in parallel with the receiving unit S1 and is powered by the load resistor R. E Power supply, transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi With receiving coil L si Through mutual inductance M i coupling.

[0251] The coupled inductor T1 includes self-inductance L1, L2 and mutual inductance M 12 , the coupled inductor T2 includes self-inductance L3, L4 and mutual inductance M 34 , L1 is connected in series with C1, L3 is connected in series with C2, L2 is connected in series with L pi Connect in series, L4 and L si Series connection, such as Fig.28 As shown, the coupled inductors T1 and T2 are isolated structures, L1 and L2 have no electrical connection, and are connected through mutual inductance M 12 Realize magnetic flux coupling; Similarly, L3 and L4 have no electrical connection, through mutual inductance M 34 Achieve flux coupling. Similar Fig.25 In the given coupled inductor structure, L1 and L2, L3 and L4 can also be connected in series in the forward direction.

[0252] Fig.28 The parameters of the resonant element meet the following requirements:

[0253]

[0254] Where ω0 is the resonant frequency. According to the basic circuit theory, the output voltage gain at the resonant frequency ω0 can be obtained as:

[0255]

[0256]

[0257] in, is the output voltage, k v , k i Mutual inductance M v 、M i Under the full compensation condition, the output voltage gain of the eleventh embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k i =ak v +b=ak+b, a and b are constants, k is the coupling coefficient, and the maximum point of the output voltage gain and the corresponding coupling coefficient k can be obtained. e for:

[0258]

[0259] G vi (k) represents the output voltage gain when the coupling coefficient is k, G vi (k e ) is k=k e The output voltage gain at this time, further, the output voltage gain is calibrated with the maximum value,

[0260]

[0261] G vi *(k) represents the output voltage gain after standardization when the coupling coefficient is k, and its expression is the same as the output voltage gain after standardization in the second embodiment of the present invention. In a given coupling coefficient interval [k min , k max ] to achieve minimal output voltage fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0262] Embodiment 12:

[0263] Fig.29 The circuit structure diagram of the twelfth embodiment of the wireless power transmission system with high anti-offset characteristics of the present invention is given. It includes a power supply E, a transmitting unit P1, a transmitting unit P2, a receiving unit S1, a receiving unit S2 and an equivalent load resistor R E . Power source E is an AC current source It can also be obtained by converting an AC voltage source plus an LC resonant network; the transmitting unit P1 includes a transmitting coil L connected in seriespv and resonant capacitor C pv ; The transmitting unit P2 includes a coupling inductor T1, a resonant capacitor C1, and a transmitting coil L pi and resonant capacitor C psi , where L pi and C psi Connected in series; the receiving unit S1 includes a receiving coil L sv and resonant capacitor C ssv , C spv , where L sv and C ssv After connecting in series with capacitor C spv The receiving unit S2 includes a receiving coil L connected in series si and resonant capacitor C si The transmitting unit P1 and the transmitting unit P2 are connected in parallel and powered by the power supply E. The receiving unit S1, the receiving unit S2 and the load resistor R E Connected in series, the transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi With receiving coil L si Through mutual inductance M i coupling.

[0264] like Fig.29 As shown, the coupled inductor T1 includes self-inductance L1, L2 and mutual inductance M 12 , L1 and C1 are connected in series, L2 and L pi Series connection, coupled inductor T1 is an isolated structure, L1 and L2 are not electrically connected, through mutual inductance M 12 Achieve flux coupling. Fig.25 Given the coupled inductor structure, L1 and L2 can also be connected in series in the forward direction. Fig.25 , receiving side resonant capacitor C spv It can also be replaced by a coupled inductor.

[0265] Fig.29 The parameters of the resonant element meet the following requirements:

[0266]

[0267] Where ω0 is the resonant frequency. According to the basic circuit theory, the output current gain at the resonant frequency ω0 can be obtained as:

[0268]

[0269]

[0270] in, is the output current, k v , k i Mutual inductance M v 、M i Under the full compensation condition, the output current gain of the twelfth embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k i =ak v +b=ak+b, a and b are constants, k is the coupling coefficient, and the maximum point of the output current gain and the corresponding coupling coefficient k can be obtained. e for:

[0271]

[0272] G ii (k) represents the output current gain when the coupling coefficient is k, G ii (k e ) is k=k e The output current gain at this time, further, the output current gain is calibrated with the maximum value,

[0273]

[0274] G ii *(k) represents the output current gain after standardization when the coupling coefficient is k. Its expression can be found to be the same as the output voltage gain after standardization in the second embodiment of the present invention. Therefore, by designing In a given coupling coefficient interval [k min , k max ] to achieve minimal output current fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0275] Embodiment 13:

[0276] Fig.30 The circuit structure diagram of the thirteenth embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. Transmitting unit P1, transmitting unit P2, receiving unit S1, receiving unit S2 and load resistor R E The transmitting unit P1 includes a transmitting coil L pv ; The transmitting unit P2 includes a transmitting coil L pi , resonant capacitor C psi and C ppi , where the transmitting coil L pi With capacitor C psi After connecting in series with capacitor C ppi Connected in parallel; the receiving unit S1 includes a receiving coil L sv ; The receiving unit S2 includes a receiving coil L si, resonant capacitor C spi and C ssi , where the receiving coil L si With capacitor C ssi After connecting in series with capacitor C spi Connect in parallel. AC voltage source Connected in series with the transmitting unit P1 and the transmitting unit P2, the receiving unit S2, the receiving unit S1 and the load resistor R E Connect in series, the transmitting coil L pv and receiving coil L sv Through mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0277] The resonant element parameters satisfy:

[0278]

[0279] Among them, ω0 is the resonant frequency. According to the basic circuit theory, the winding current corresponding to the resonant frequency ω0 can be obtained as

[0280]

[0281] in and The current flowing through the transmitting coil L pv , transmitting coil L pi , receiving coil L si and receiving coil L sv Further, the output current gain and input impedance of the thirteenth embodiment of the present invention are:

[0282]

[0283]

[0284] in, is the output current, k v , k i Mutual inductance M v 、M i It can be seen that under the condition of full compensation, the output current gain of the thirteenth embodiment of the present invention has nothing to do with the load, and the input impedance is always pure resistance. Let k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the maximum point of the output current gain and the corresponding coupling coefficient k can be obtained. e for:

[0285]

[0286] Furthermore, the output current gain is normalized by the maximum value, and we have

[0287]

[0288] G iw *(k) represents the output current gain after standardization when the coupling coefficient is k. Its expression is the same as the output voltage gain expression after standardization in the second embodiment of the present invention. It changes non-monotonically with the coupling coefficient and changes slowly near the extreme point. Therefore, by designing In a given coupling coefficient interval [k min , k max ] to achieve minimal output current fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0289] The transmitting coil L in the thirteenth embodiment of the present invention pv , transmitting coil L pi , receiving coil L si and receiving coil L sv The self-inductance value is also required to satisfy:

[0290] λ p =L pv / L pi ,λ s =L sv / L si (85)

[0291] Embodiment 14:

[0292] Fig.31 The circuit structure diagram of the fourteenth embodiment of the wireless power transmission system with high anti-deviation characteristics of the present invention is given. Transmitting unit P1, transmitting unit P2, receiving unit S1, receiving unit S2, rectifier filter circuit R and load resistor R L The transmitting unit P1 includes a transmitting coil L connected in series. pv and resonant capacitor C pv ; The transmitting unit P2 includes a transmitting coil L connected in parallel pi and resonant capacitor C ppi The receiving unit S1 includes a receiving coil L connected in series sv and resonant capacitor C sv The receiving unit S2 includes a receiving coil L connected in parallel si and resonant capacitor C spi . AC voltage source Connected in series with the transmitting unit P1 and the transmitting unit P2, the receiving unit S2, the receiving unit S1 and the load resistor R E Connect in series, the transmitting coil L pv and receiving coil L sv Mutual inductance M v Coupling, transmitting coil L pi and receiving coil L si Through mutual inductance M i coupling.

[0293] The resonant element parameters satisfy:

[0294]

[0295] Where ω0 is the resonant frequency. When working at the resonant frequency ω0, according to the basic circuit theory, the output current gain and input impedance can be deduced as follows:

[0296]

[0297]

[0298] in, is the output current k v , k i Mutual inductance M v 、M i The corresponding coupling coefficient. The winding current, output current gain and input impedance expressions given in the thirteenth embodiment of the present invention are the same, and the fourteenth embodiment of the present invention has similar performance to the thirteenth embodiment. Under the full compensation condition, the output current gain of the fourteenth embodiment of the present invention is independent of the load, and the input impedance is always pure resistance. Let k v =ak i +b=ak+b, a and b are constants, k is the coupling coefficient, and the maximum point of the output current gain and the corresponding coupling coefficient k can also be obtained. e for:

[0299]

[0300] G iv (k) represents the output current gain when the coupling coefficient is k, G iv (k e ) is k=k e The output current gain at this time, further, the output current gain is calibrated with the maximum value,

[0301]

[0302] G iv*(k) represents the output current gain after standardization when the coupling coefficient is k. Its expression is the same as the output voltage gain expression after standardization in the second embodiment of the present invention. It changes non-monotonically with the coupling coefficient and changes slowly near the extreme point. Therefore, by designing In a given coupling coefficient interval [k min , k max ] to achieve minimal output current fluctuation and improve the anti-offset characteristics of the wireless power transmission system.

[0303] Embodiment 14 of the present invention requires that the transmitting coil L pv , transmitting coil L pi , receiving coil L si and receiving coil L sv The self-sensitivity value satisfies

[0304]

[0305] It can be in the effective coupling coefficient range [k min , k max ] to achieve minimal output current fluctuation ξ.

[0306] Test example 1:

[0307] In order to verify the feasibility of the present invention, Fig.23 The wireless power transmission system with high anti-deviation characteristics shown in the figure is used as an example. Figure 1 The non-contact transformer structure shown in the figure was experimentally verified. The following table shows the specific values ​​of the primary and secondary self-inductance and compensation capacitance of the non-contact transformer used in this test when the air gap is 5cm. The mutual inductance and coupling coefficient curves of the non-contact transformer used in this test at different air gap spacings are shown in Fig.32 As shown in the figure, it can be seen that the mutual inductances M1, M2, M3 and M4 of the non-contact transformer structure 1 used in the present invention are always very small, approximately zero, and the mutual inductance M i and M v As the air gap spacing increases, it decreases by approximately the same amount.

[0308] Table 1: Resonant element parameters

[0309]

[0310] The input voltage V in is 50V, the resonant frequency f0 is 85kHz, then ω0=2πf0, the effective coupling coefficient range is [0.117, 0.4], and the DC output current measured at different air gap spacing is as follows Fig.33As shown, it can be seen that the wireless power transmission system with high anti-offset characteristics proposed in the present invention can effectively improve the stability of the output characteristics of the contactless power supply system under offset conditions, while maintaining the output stability of the output voltage characteristics under variable load conditions. Within the range of 3.4 times the coupling coefficient, the output current fluctuation ξ is only 1.2.

[0311] Test Example 2:

[0312] In order to verify the feasibility of the present invention, Fig.18 The wireless power transmission system with high anti-deviation characteristics shown in the figure is used as an example. Figure 1 The non-contact transformer structure shown in the figure was experimentally verified. The following table shows the specific values ​​of the primary and secondary self-inductance and compensation capacitance of the non-contact transformer used in this test when the air gap is 5cm. The mutual inductance and coupling coefficient curves of the non-contact transformer used in this test at different air gap spacings are shown in Fig.32 As shown in the figure, it can be seen that the mutual inductances M1, M2, M3 and M4 of the non-contact transformer structure 1 used in the present invention are always very small, approximately zero, and the mutual inductance M i and M v As the air gap spacing increases, it decreases by approximately the same amount.

[0313] Table 2: Resonant element parameters

[0314]

[0315] The input voltage V in is 50V, the resonant frequency f0 is 85kHz, then ω0=2πf0, the effective coupling coefficient range is [0.117, 0.4], and the DC output voltage measured at different air gap spacing is as follows Fig.34 As shown in the figure, it can be seen that the wireless power transmission system with high anti-offset characteristics proposed in the present invention can effectively improve the stability of the output characteristics of the non-contact power supply system under offset conditions, while maintaining the output stability of the output voltage characteristics under variable load conditions. Within the range of 3.4 times the coupling coefficient, the output voltage fluctuation ξ v Only 1.2.

[0316] The above is only a preferred embodiment of the present invention. It should be pointed out that for ordinary technicians in this technical field, several improvements and modifications can be made without departing from the principle of the present invention. These improvements and modifications should also be regarded as the scope of protection of the present invention.

Claims

1. A wireless power transmission system with high anti-deviation characteristics, characterized in that: Power supply included E , transmitting unit P1, transmitting unit P2, receiving unit S1, receiving unit S2, rectification and filtering circuit and load resistance; The transmitting unit P1 includes a transmitting coil T1 and an impedance unit Z01 connected in series; The transmitting unit P2 includes a transmitting coil T2, a series impedance unit Z02a and a parallel impedance unit Z02b, wherein T2 is connected in series with Z02a and then connected in parallel with Z02b, or T2 is connected in parallel with Z02b and then connected in series with Z02a; The receiving unit S1 comprises a receiving coil R1 and an impedance unit Z03 connected in series; The receiving unit S2 comprises a receiving coil R2, a series impedance unit Z04a and a parallel impedance unit Z04b, R2 is connected in series with Z04a and then connected in parallel with Z04b, or R2 is connected in parallel with Z04b and then connected in series with Z04a; The impedance units Z01, Z03, Z02a, and Z04a are wires or single inductors or single capacitors or a combination of multiple inductors and capacitors connected in series or in parallel; The impedance unit Z02 and / or Z04 is a single inductor or a single capacitor or a combination of multiple inductors and capacitors connected in series or in parallel; Wherein: the power supply E is connected in series with the transmitting unit P1 and the transmitting unit P2 in sequence, the receiving unit S2, the receiving unit S1, the rectifier filter circuit and the load resistor are connected in series in sequence, and the transmitting coil T1 and the receiving coil R1 are connected in series via mutual inductance M v The transmitting coil T2 and the receiving coil R2 are coupled by mutual inductance. M i coupling; Or the power source E is connected in series with the transmitting unit P1 and the transmitting unit P2 in sequence, the receiving unit S1 is connected in parallel with the receiving unit S2 and then connected in series with the rectifier filter circuit and the load resistor in sequence, and the transmitting coil T1 and the receiving coil R2 are connected via mutual inductance. M v The transmitting coil T2 and the receiving coil R1 are coupled by mutual inductance. M i coupling; Or the transmitting unit P1 and the transmitting unit P2 are connected in parallel and powered by the power supply E, the receiving unit S2, the receiving unit S1, the rectifier filter circuit and the load resistor are connected in series in sequence, and the transmitting coil T1 and the receiving coil R2 are connected by mutual inductance. M v The transmitting coil T2 and the receiving coil R1 are coupled by mutual inductance. M i coupling; Or the transmitting unit P1 and the transmitting unit P2 are connected in parallel and powered by the power supply E, the receiving unit S1 and the receiving unit S2 are connected in parallel and connected in series with the rectifier filter circuit and the load resistor in sequence, and the transmitting coil T1 and the receiving coil R1 are connected by mutual inductance. M v The transmitting coil T2 and the receiving coil R2 are coupled by mutual inductance. M i coupling; The conductors of the transmitting coil and the receiving coil are both made of solid conductors, Litz wires, copper sheets, copper tubes or PCB windings.

2. A wireless power transmission system with high anti-deviation characteristics according to claim 1, characterized in that: By setting the coil structures and phase positions of the transmitting coil T1, the transmitting coil T2, the receiving coil R1 and the receiving coil R2, there is no magnetic flux coupling or weak magnetic coupling between the transmitting coil T1 and the transmitting coil T2, between the transmitting coil T1 and the receiving coil R1, between the transmitting coil T2 and the receiving coil R1, and between the receiving coil R1 and the receiving coil R2 in the absence of offset.

3. A wireless power transmission system with high anti-deviance characteristics according to claim 1 or 2, characterized in that: The power supply E It is an AC constant voltage source or an AC constant current source, or is composed of a DC voltage source and a high-frequency inverter connected to each other, or is composed of a constant current source plus an LC network.

4. A wireless power transmission system with high anti-deviance characteristics according to claim 1 or 2, characterized in that: The coil structures of the transmitting coil T1, transmitting coil T2, receiving coil R1, and receiving coil R2 are single coil structures, double coil structures, multi-coil structures, or solenoid structures, and the structures of the primary magnetic core and / or the secondary magnetic core are U-shaped, I-shaped, edge-extended types in which the bottoms of the two side columns extend outward along the sides, cross-shaped, or a combination of the above structures.

5. A wireless power transmission system with high anti-deviance characteristics according to claim 1 or 2, characterized in that: The impedance unit Z02b and / or Z04b is a coupled inductor.

6. A wireless power transmission system with high anti-deviance characteristics according to claim 3, characterized in that: The AC constant current source is obtained by adding an LC network to an AC constant voltage source.

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