A dielectric waveguide resonator and a multimode dielectric waveguide resonator
By introducing a metal loading interface and a blind hole structure into the dielectric waveguide resonator, the electric field oscillation path is adjusted, which solves the problem of narrow bandwidth of dielectric waveguide filters when balancing power capacity and unloaded Q value, and achieves bandwidth expansion and loss improvement.
Patent Information
- Authority / Receiving Office
- CN · China
- Patent Type
- Patents(China)
- Current Assignee / Owner
- SHENZHEN SAMSUNG COMM TECH RES
- Filing Date
- 2021-10-26
- Publication Date
- 2026-06-26
AI Technical Summary
Existing dielectric waveguide filters present a contradiction in balancing power capacity, unloaded Q value, and channel bandwidth. The standard rectangular waveguide TE10 mode has a narrow channel bandwidth, while the unloaded Q value of the quasi-TEM mode with a blind aperture is reduced, resulting in a tradeoff between filter size and parameters.
By adding a metal loading interface to the dielectric body of the dielectric waveguide resonator and adjusting the electric field oscillation path through a blind hole structure, the main mode frequency is reduced and the bandwidth between the higher-order mode frequency and the main frequency is extended, thereby improving the performance of the low-pass filter.
Without changing the size of the dielectric waveguide resonator or the unloaded Q value, the bandwidth between the higher-order mode frequency and the dominant frequency is increased, thus improving the loss performance of the low-pass filter.
Smart Images
Figure CN116031602B_ABST
Abstract
Description
Technical Field
[0001] This invention relates to the field of communication technology, and in particular to a dielectric waveguide resonator and a multimode dielectric waveguide resonator. Background Technology
[0002] There are two common types of resonator units used in dielectric waveguide filters: the standard rectangular waveguide TE10 mode and the quasi-TEM mode with blind apertures.
[0003] Among them, the dielectric waveguide filter of the standard rectangular waveguide TE10 mode has the advantages of large power capacity and large unloaded Q value, but its higher-order mode frequency is close to the main mode frequency and the channel bandwidth is narrow.
[0004] While quasi-TEM mode dielectric waveguide filters with blind apertures extend higher-order mode frequencies and broaden channel bandwidth, their unloaded Q-factor decreases. To compensate for the structural losses, the size of the dielectric waveguide filter must be increased, resulting in a tradeoff between the filter's size and parameters. Summary of the Invention
[0005] This application provides a dielectric waveguide resonator and a multimode dielectric waveguide resonator. By adding a metal loading interface to the dielectric body of the dielectric waveguide resonator, the dominant mode frequency of the waveguide resonator is reduced while keeping the size and unloaded Q value of the dielectric waveguide resonator unchanged. This increases the bandwidth between the higher-order mode frequency and the dominant frequency, improves the performance of the low-pass filter, and reduces losses.
[0006] This application provides a dielectric waveguide resonator, including:
[0007] A dielectric resonant cavity, the dielectric resonant cavity comprising a dielectric body and a metal plating layer surrounding the outer surface of the dielectric body;
[0008] A metal loading interface is disposed within the medium body and is in contact with the metal plating layer.
[0009] The metal loading interface intersects with the intrinsic electric field direction of the dielectric resonant cavity to reduce the dominant mode frequency of the dielectric resonant cavity.
[0010] In one embodiment, it further includes:
[0011] A blind hole is recessed inward from the surface of the dielectric body. The bottom surface of the blind hole located inside the dielectric body is the metal loading interface. The axial direction of the blind hole is consistent with the intrinsic electric field direction of the dielectric resonant cavity.
[0012] In one embodiment, the blind hole includes a first blind hole and a second blind hole, the first blind hole and the second blind hole being recessed inward from a pair of opposing surfaces of the dielectric body, the pair of opposing surfaces being perpendicular to the intrinsic electric field direction of the dielectric resonant cavity;
[0013] The bottom surface of the first blind hole located within the medium body is a first metal loading interface, and the bottom surface of the second blind hole located within the medium body is a second metal loading interface. The first metal loading interface and the second metal loading interface have a gap between them and at least partially overlap each other.
[0014] In one embodiment, the diameters of the first metal loading interface and the second metal loading interface are different.
[0015] In one embodiment, the centers of the first metal loading interface and the second metal loading interface are aligned with each other.
[0016] In one embodiment, the spacing is associated with the higher-order mode frequency.
[0017] In one embodiment, at least one of the first blind hole and the second blind hole is a stepped hole.
[0018] In one embodiment, the cross-sectional dimensions of the stepped hole gradually decrease in the direction from the surface of the medium body inward.
[0019] Another embodiment of the present invention provides a multimode dielectric waveguide resonator, comprising:
[0020] Multiple dielectric waveguide resonators as described above;
[0021] Two adjacent dielectric waveguide resonators are coupled through a coupling window.
[0022] In one embodiment, the metal loading interfaces of two adjacent dielectric waveguide resonators have different shapes.
[0023] In this embodiment, the intrinsic electric field direction of the dielectric resonator is the direction between a pair of opposing surfaces connected to the dielectric body. The metal loading interface is a metal surface located between these opposing surfaces, intersecting the intrinsic electric field direction of the dielectric resonator and situated at the location of the strongest dominant mode. This causes the electromagnetic waves within the dielectric resonator to oscillate between the metal loading interface and one of the opposing surfaces, rather than between the opposing surfaces themselves, thereby reducing the oscillation space of the electromagnetic waves and forming a capacitive loading structure within the dielectric resonator. The presence of the metal loading interface not only alters the oscillation distance of the electromagnetic waves but also changes the direction of the local electric field, thus reducing the dominant mode frequency of the dielectric resonator.
[0024] In this embodiment, the metal loading interface is applied to the position where the dominant mode of the dielectric resonator is strongest. Since the setting of the metal loading interface does not affect the size and structure of the dielectric body, it does not affect the size of the dielectric resonator itself or the unloaded Q value. However, by reducing the dominant mode frequency, the distance between the dominant mode frequency and the higher-order mode frequency is increased, thereby expanding the bandwidth and improving the performance of the low-pass filter and reducing the loss. Attached Figure Description
[0025] To more clearly illustrate the technical solutions of the embodiments of the present invention, the drawings used in the description of the embodiments of the present invention will be briefly introduced below. Obviously, the drawings described below are only some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without creative effort.
[0026] Figure 1 This is a schematic diagram of the dielectric waveguide resonator of the present invention.
[0027] Figure 2a and Figure 2b These are the electric field vector diagrams for the primary mode frequency and higher-order mode frequency of the dielectric waveguide resonator of this invention.
[0028] Figure 3 This is a schematic diagram of the structure of the first embodiment of the dielectric waveguide resonator of the present invention.
[0029] Figure 4 for Figure 3 Vector diagram of the electric field direction of a dielectric waveguide resonator.
[0030] Figure 5 This is a schematic diagram of the structure of a second embodiment of the dielectric waveguide resonator of the present invention.
[0031] Figure 6 This is a schematic diagram of the third embodiment of the dielectric waveguide resonator of the present invention.
[0032] Figure 7 This is a schematic diagram of the structure of the multimode dielectric waveguide resonator of the present invention. Detailed Implementation
[0033] To better understand the above technical solutions, exemplary embodiments of this application will be described in detail below with reference to the accompanying drawings. Obviously, the described embodiments are only a part of the embodiments of this application, and not all of the embodiments of this application. It should be understood that this application is not limited to the exemplary embodiments described herein.
[0034] This application provides a dielectric waveguide resonator and a multimode dielectric waveguide resonator. By adding a metal loading interface to the dielectric body of the dielectric waveguide resonator, higher-order mode harmonics are pushed away while keeping the size, frequency, and unloaded Q value of the dielectric waveguide resonator unchanged, thus improving the performance of the low-pass filter and reducing losses.
[0035] Figure 1 This is a schematic diagram of the dielectric waveguide resonator of the present invention. Figure 2a and Figure 2b These are the electric field vector diagrams for the primary mode frequency and higher-order mode frequency of the dielectric waveguide resonator of this invention.
[0036] like Figures 1 to 2b As shown, one embodiment of the present invention provides a dielectric waveguide resonator 1, characterized in that it comprises:
[0037] The dielectric resonant cavity 10 includes a dielectric body 11 and a metal plating layer 12 that surrounds the outer surface of the dielectric body 11.
[0038] Metal loading interface 20 is disposed within the medium body 11 and is in contact with the metal plating layer 12.
[0039] The metal loading interface 20 intersects with the intrinsic electric field direction of the dielectric resonant cavity 10 to reduce the dominant mode frequency of the dielectric resonant cavity 10.
[0040] exist Figure 1 In the illustrated embodiment, the intrinsic electric field direction of the dielectric resonant cavity 10 is connected to a pair of opposing surfaces of the dielectric body 11 (e.g., ...). Figure 2a The direction is indicated by the downward arrow. The metal loading interface 20 is a metal surface located between these opposing surfaces, intersecting the intrinsic electric field direction of the dielectric resonator 10, and located at the position where the dominant mode of the dielectric resonator 10 is strongest (usually the center of the pair of surfaces). This causes the electromagnetic waves within the dielectric resonator 10 to oscillate between the metal loading interface 20 and one of the opposing surfaces, rather than between the opposing surfaces themselves, thereby reducing the oscillation space of the electromagnetic waves and forming a capacitive loading structure in the dielectric resonator 10. The presence of the metal loading interface 20 not only changes the oscillation distance of the electromagnetic waves but also changes the direction of the local electric field, such as... Figure 2a As shown, it reduces the dominant mode frequency of the dielectric resonator 10.
[0041] In this embodiment, the metal loading interface 20 is loaded at the position where the main mode of the dielectric resonator 10 is strongest. Since the setting of the metal loading interface 20 does not affect the size and structure of the dielectric body 11, it does not affect the size and unloaded Q value of the dielectric resonator 10 itself. However, by reducing the main mode frequency of the dielectric resonator 10, the distance between the higher-order mode frequency and the main mode frequency is increased, thereby expanding the bandwidth, improving the performance of the low-pass filter, and improving the loss.
[0042] In one specific embodiment, the dielectric resonator 10 further includes:
[0043] Blind hole 30 is recessed inward from the surface of dielectric body 11. The surface of blind hole 30 is covered with a metal plating layer. The bottom surface of blind hole 30 located inside dielectric body 11 is a metal loading interface 20. The axial direction of blind hole 30 is consistent with the intrinsic electric field direction of dielectric resonant cavity 10.
[0044] The blind hole 30 is an embodiment of forming a metal loading interface 20 within the dielectric body 11. The blind hole 30 does not penetrate the dielectric body 11 in the intrinsic electric field direction of the dielectric resonant cavity 10, but forms a gap between the side surface opposite to the recessed surface. This gap is smaller than the distance between the two surfaces (e.g., the length, width, and height of the dielectric body), thus forming a reduced oscillation space and thereby changing the position of the main mode frequency.
[0045] The axial direction of the blind hole 30 can be consistent with the intrinsic electric field direction of the dielectric resonant cavity 10, and the bottom surface, that is, the cross-sectional shape of the blind hole 30, can be selected as circular, elliptical, rectangular, square, etc. Figure 1 The shape is shown as circular. The axial length (e.g., height) of the blind aperture 30 can be correlated with the location of the dominant mode frequency of the dielectric resonator 10.
[0046] There may be more than one metal loading interface within the dielectric body 11. The dielectric body 11 may have multiple opposing metal loading interfaces to adjust the electric field oscillation space within the dielectric body 11.
[0047] In such Figure 3 In the first embodiment shown, the blind hole 30 includes a first blind hole 30a and a second blind hole 30b. The first blind hole 30a and the second blind hole 30b are recessed inward from a pair of opposing surfaces of the dielectric body 11, and the pair of opposing surfaces are perpendicular to the intrinsic electric field direction of the dielectric resonant cavity 10.
[0048] The bottom surface of the first blind hole 30a located inside the dielectric body 11 is the first metal loading interface 20a, and the bottom surface of the second blind hole 30b located inside the dielectric body 11 is the second metal loading interface 20b. The first metal loading interface 20a and the second metal loading interface 20b have a gap between them and at least partially overlap each other to form an electric field oscillation space between the first metal loading interface 20a and the second metal loading interface 20b.
[0049] This embodiment and Figure 1 Compared to the embodiment shown, decomposing a blind hole into a pair of blind holes that are recessed from a pair of opposing surfaces can significantly reduce the height of a single blind hole while achieving the same electric field oscillation space. This improves the adjustment range of the dielectric resonator 10 and reduces the fabrication difficulty of the dielectric waveguide filter in this embodiment.
[0050] In such Figure 3 In the illustrated embodiment, the first metal loading interface 20a and the second metal loading interface 20b have different diameters. In a preferred embodiment, the centers of the first metal loading interface 20a and the second metal loading interface 20b are aligned with each other, and they can coincide with the center points of the pair of opposing surfaces of the medium body 11.
[0051] like Figure 4 As shown, these metal loading interfaces of different sizes can form an electric field direction with an angle to the intrinsic electric field direction (i.e., the main mode direction) between the edges of the first metal loading interface 20a and the second metal loading interface 20b. The direction obtained after orthogonally decomposing the electric field direction helps to enhance the main mode direction component and push back the higher-order mode frequency.
[0052] In this embodiment, the spacing between a pair of metal loading interfaces is related to the position of the master mode frequency. For example, the smaller the spacing between a pair of metal loading interfaces, the farther the position of the higher mode frequency is from the position of the master mode frequency.
[0053] The cross-sectional shape of the blind hole 30 can be selected as follows: Figure 1 and Figure 3 The axial dimension (diameter) of the blind aperture 30 shown can remain constant, or it can be selected to vary stepwise or gradually along the axial direction of the blind aperture 30. The cross-sectional dimension of the blind aperture 30 affects the unloaded Q value of the dielectric resonator 10. To avoid the blind aperture reducing the unloaded Q value of the dielectric resonator 10, this effect can be reduced by locally reducing the cross-sectional dimension of the blind aperture 30.
[0054] For example, Figure 5 and Figure 6 As shown, at least one of the first blind hole 30a and the second blind hole 30b is a stepped hole.
[0055] exist Figure 5 In the illustrated embodiment, the first blind hole 30a is a stepped hole, while the second blind hole 30b is a cylindrical hole with unchanged cross-sectional dimensions. And... Figure 6 In the embodiment shown, both the first blind hole 30a and the second blind hole 30b are stepped holes.
[0056] In order to facilitate processing and to consider the influence of the cross-sectional size of the blind hole on the unloaded Q value, the cross-sectional size of the stepped hole gradually decreases in the direction from the surface of the medium body 11 inward (main mold direction).
[0057] When a blind hole is a stepped hole, its metal loading interface is the smallest cross-section located at the bottom of the blind hole. This can be imagined as... Figure 1 In the case shown, which has a single blind hole, the blind hole can also be implemented as a stepped hole.
[0058] exist Figure 5 and Figure 6 As can be seen in the second and third embodiments shown, by combining various parameters such as the number of blind holes, cross-sectional size, and cross-sectional shape, the dielectric waveguide resonator of the present invention can simultaneously reduce the dominant mode frequency and push back the higher-order mode frequencies. Furthermore, the diverse adjustment methods can lead to an expanded range of adjustment parameters, thereby achieving optimal performance without changing the size of the dielectric resonator cavity. It is also conceivable that the dielectric waveguide resonator of the present invention can significantly reduce the size of the resonator cavity while maintaining the same performance.
[0059] like Figure 7 As shown, another embodiment of the present invention also provides a multimode dielectric waveguide resonator 100, comprising:
[0060] Multiple such as Figure 1 , Figures 3 to 6 The dielectric waveguide resonator 1 shown in any of the images is coupled between two adjacent dielectric waveguide resonators 1 through a coupling window 2.
[0061] In one specific embodiment, the dielectric bodies 11 of two adjacent dielectric waveguide resonators 1 can be integrally formed, with their outer surfaces covered by a metal plating layer that is integrally connected. A coupling window 2 is formed between the two adjacent dielectric waveguide resonators 1, and it can be a window recessed from the surface of the dielectric body 11. In a preferred embodiment, the surface of the coupling window 2 may be different from or the same as the surface of the blind via 30.
[0062] In a preferred embodiment, two adjacent dielectric waveguide resonators 1 are of different types, specifically, their metal loading interfaces 20 have different shapes, i.e., the cross-sectional shapes of the blind holes 30 are different.
[0063] For example, in Figure 7In the example shown, one of the dielectric waveguide resonators 1 has a pair of stepped blind holes 30a and 30b with a rectangular metal loading cross-section, while the other dielectric waveguide resonator 1 has a pair of stepped blind holes 30a' and 30b' with a circular metal loading cross-section.
[0064] Alternatively, two adjacent dielectric waveguide resonators 1 may be of different types, and may also have different numbers of metal loading interfaces 20. For example, one dielectric waveguide resonator 1 may have one metal loading interface, while the other dielectric waveguide resonator 1 may have a pair of metal loading interfaces.
[0065] Alternatively, two adjacent dielectric waveguide resonators 1 can be of different types, or their metal loading interfaces 20 can be of different sizes, and so on.
[0066] Having two adjacent dielectric waveguide resonators 1 of different types can avoid coupling of the main mode frequencies of the two dielectric waveguide resonators 1.
[0067] In the dielectric waveguide resonator and multimode dielectric waveguide resonator of the present invention, the intrinsic electric field direction of the dielectric resonator is the direction between a pair of opposing surfaces connected to the dielectric body. The metal loading interface is a metal surface located between these opposing surfaces, intersecting the intrinsic electric field direction of the dielectric resonator and situated at the position where the dominant mode of the dielectric resonator is strongest. This causes the electromagnetic (magnetic) waves within the dielectric resonator to oscillate between the metal loading interface and one of the opposing surfaces, rather than between the opposing surfaces themselves, thereby reducing the oscillation space of the electromagnetic (magnetic) waves and forming a capacitive loading structure within the dielectric resonator. The presence of the metal loading interface not only changes the oscillation distance of the electromagnetic (magnetic) waves but also alters the direction of the local electric field, thus reducing the dominant mode frequency of the dielectric resonator 10.
[0068] In this embodiment, the metal loading interface is applied to the position where the dominant mode of the dielectric resonator is strongest. Since the setting of the metal loading interface does not affect the size and structure of the dielectric body, it does not affect the size of the dielectric resonator itself or the unloaded Q value. However, by reducing the dominant mode frequency of the dielectric resonator 10, the distance between the higher-order mode frequency and the dominant mode frequency is increased, thus expanding the bandwidth and improving the performance of the low-pass filter and reducing loss.
[0069] The basic principles of this application have been described above with reference to specific embodiments. However, it should be noted that the advantages, benefits, and effects mentioned in this application are merely examples and not limitations, and should not be considered as essential features of each embodiment of this application. Furthermore, the specific details disclosed above are for illustrative and facilitative purposes only, and are not limitations. These details do not limit the application to the necessity of employing the aforementioned specific details for implementation.
[0070] The block diagrams of devices, apparatuses, devices, and systems involved in this application are merely illustrative examples and are not intended to require or imply that they must be connected, arranged, or configured in the manner shown in the block diagrams. As those skilled in the art will recognize, these devices, apparatuses, devices, and systems can be connected, arranged, and configured in any manner. Words such as “comprising,” “including,” “having,” etc., are open-ended terms meaning “including but not limited to,” and are used interchangeably with them. The terms “or” and “and” as used herein refer to the terms “and / or,” and are used interchangeably with them unless the context clearly indicates otherwise. The term “such as” as used herein refers to the phrase “such as but not limited to,” and is used interchangeably with it.
[0071] It should also be noted that in the apparatus, equipment, and methods of this application, the components or steps can be disassembled and / or recombined. These disassemblies and / or recombinations should be considered as equivalent solutions of this application.
[0072] The above description of the disclosed aspects is provided to enable any person skilled in the art to make or use this application. Various modifications to these aspects will be readily apparent to those skilled in the art, and the general principles defined herein can be applied to other aspects without departing from the scope of this application. Therefore, this application is not intended to be limited to the aspects shown herein, but rather to be accorded the widest scope consistent with the principles and novel features disclosed herein.
[0073] The above description has been given for illustrative and descriptive purposes. Furthermore, this description is not intended to limit the embodiments of this application to the forms disclosed herein. Although numerous exemplary aspects and embodiments have been discussed above, those skilled in the art will recognize that certain variations, modifications, alterations, additions, and sub-combinations thereof should be included within the scope of protection of this invention.
Claims
1. A dielectric waveguide resonator (1), characterized in that, include: The dielectric resonant cavity (10) includes a dielectric body (11) and a metal plating layer (12) that surrounds the outer surface of the dielectric body (11). A first blind hole (30a) and a second blind hole (30b) are respectively recessed inward from a pair of opposing surfaces of the dielectric body (11). The pair of opposing surfaces are perpendicular to the intrinsic electric field direction of the dielectric resonant cavity (10). The axial directions of the first blind hole (30a) and the second blind hole (30b) are both parallel to the intrinsic electric field direction. Metal loading interface (20), the metal loading interface (20) includes a first metal loading interface (20a) and a second metal loading interface (20b), the first metal loading interface (20a) and the second metal loading interface (20b) are disposed in the medium body (11) and are in contact with the metal plating layer (12); The bottom surface of the first blind hole (30a) located within the medium body (11) is the first metal loading interface (20a), and the bottom surface of the second blind hole (30b) located within the medium body (11) is the second metal loading interface (20b). The first metal loading interface (20a) and the second metal loading interface (20b) have a gap between them and at least partially overlap each other. The metal loading interface (20) intersects the intrinsic electric field direction of the dielectric resonant cavity (10), and the spacing and the size of the first metal loading interface and / or the second metal loading interface are configured to: reduce the dominant mode frequency of the dielectric resonant cavity (10) and increase the bandwidth between the higher-order mode frequency and the dominant frequency.
2. The dielectric waveguide resonator (1) according to claim 1, characterized in that, The diameters of the first metal loading interface (20a) and the second metal loading interface (20b) are different.
3. The dielectric waveguide resonator (1) according to claim 1, characterized in that, The centers of the first metal loading interface (20a) and the second metal loading interface (20b) are aligned with each other.
4. The dielectric waveguide resonator (1) according to claim 1, characterized in that, At least one of the first blind hole (30a) and the second blind hole (30b) is a stepped hole.
5. The dielectric waveguide resonator (1) according to claim 4, characterized in that, The cross-sectional dimensions of the stepped hole gradually decrease inward from the surface of the medium body (11).
6. A multimode dielectric waveguide resonator (100), characterized in that, include: Multiple dielectric waveguide resonators (1) as described in any one of claims 1 to 5; Two adjacent dielectric waveguide resonators (1) are coupled through a coupling window (2).
7. The multimode dielectric waveguide resonator (100) according to claim 6, characterized in that, The metal loading interface (20) of two adjacent dielectric waveguide resonators (1) has different shapes.