Antenna structure and electronic equipment

Abstract

The invention relates to an antenna structure and electronic equipment, which is characterized in that an antenna radiation layer, a negative magnetic conductivity layer and a negative dielectric constant layer are respectively arranged on a top layer, a middle layer and a bottom layer of a supporting structure, and orthographic projection parts of the negative magnetic conductivity layer and the negative dielectric constant layer in a first direction are overlapped; compact laminated layout and effective electromagnetic coupling of the three functional layers are realized. According to the design, the negative magnetic conductivity layer and the negative dielectric constant layer generate a synergistic effect to form a double-negative superconducting characteristic, and meanwhile, the radiation performance of the antenna radiation layer is improved through a strong coupling effect between the antenna radiation layer and the double-negative superconducting characteristic, so that the overall size of the antenna is remarkably reduced, and the working efficiency of the antenna in multiple working frequency bands is also improved; and a high-performance antenna solution is provided for miniaturized communication equipment.

Description

Technical Field

[0001] The present invention relates to the technical field of antenna design, and in particular to an antenna structure and electronic equipment. Background Art

[0002] With the rapid development of mobile communication technology, portable electronic devices such as laptops and tablets have put forward higher requirements for the utilization of internal space. In the prior art, consumer electronic products generally adopt traditional antenna design solutions. Such antennas usually occupy a large space, which limits the rational planning and utilization of the internal space of the product. Due to their structural characteristics, traditional antennas are difficult to miniaturize while ensuring performance, especially in modern electronic devices with more metal environments. The antenna substrate is one of the key factors affecting the performance and bandwidth of the antenna. The electromagnetic characteristics of the traditional substrate in the microwave frequency band cannot support the further miniaturization of the antenna. In recent years, superconducting materials have gradually received widespread attention in the research field of large-scale phased array unit antennas. However, this technology has not yet been widely used in the field of consumer electronics. Summary of the invention

[0003] The object of the present invention is to provide an antenna structure and an electronic device, which can enhance the radiation performance of the antenna and reduce the occupied area of ​​the antenna.

[0004] In order to solve the above technical problems, the present invention provides an antenna structure, comprising:

[0005] Support structure;

[0006] an antenna radiation layer disposed on the top layer of the support structure;

[0007] A negative magnetic permeability layer provided in the middle layer of the support structure;

[0008] and, a negative dielectric constant layer disposed on the bottom layer of the support structure;

[0009] The orthographic projection of the negative magnetic permeability layer along the first direction partially overlaps with the orthographic projection of the negative dielectric constant layer along the first direction, wherein the first direction is the direction from the antenna radiation layer to the negative dielectric constant layer.

[0010] Furthermore, the antenna radiation layer includes a low-frequency arm and a high-frequency arm;

[0011] The low frequency arm semi-surrounds the high frequency arm;

[0012] One end of the low-frequency arm is connected to the antenna feeding point, and the other end is open;

[0013] One end of the high-frequency arm is electrically connected to the antenna feeding point through the low-frequency arm, and the other end is open.

[0014] Furthermore, the low frequency arm includes a first antenna branch, a second antenna branch, a third antenna branch and a fourth antenna branch. The high frequency arm includes a fifth antenna branch, a sixth antenna branch, a seventh antenna branch, an eighth antenna branch and a ninth antenna branch;

[0015] The first antenna branch, the second antenna branch and the third antenna branch are sequentially connected to form a low-frequency radiation section with a semi-enclosed rectangular frame structure; the fifth antenna branch, the sixth antenna branch and the seventh antenna branch are sequentially connected to form a high-frequency radiation section with a semi-enclosed rectangular frame structure;

[0016] The fourth antenna branch is connected to one end of the low-frequency radiation section, and the other end of the fourth antenna branch is connected to the ninth antenna branch of the high-frequency arm; one end of the ninth antenna branch is connected to one end of the high-frequency radiation section through the eighth antenna branch, and the other end is connected to the antenna feeding point;

[0017] The other ends of the low-frequency radiation section and the high-frequency radiation section are in an open circuit state.

[0018] Furthermore, a tuning slot is provided at the connection between the fifth antenna branch and the sixth antenna branch;

[0019] The connection between the sixth antenna branch and the seventh antenna branch, and the connection between the seventh antenna branch and the eighth antenna branch are each provided with at least one resonance adjustment section.

[0020] Further, the negative magnetic permeability layer includes a concentric double ring resonator formed by an outer ring conductor surrounding an inner ring conductor;

[0021] The outer ring conductor and the inner ring conductor are both composed of microstrip lines;

[0022] The outer ring conductor is provided with a first opening along the circumferential direction, and the inner ring conductor is provided with a second opening along the circumferential direction; the first opening and the second opening are respectively located on two opposite sides of the concentric dual ring resonator.

[0023] Furthermore, the diameter of the concentric double rings is 1 / 10×λ, wherein λ is the wavelength of the electromagnetic wave.

[0024] Further, the negative dielectric constant layer;

[0025] The negative dielectric constant layer includes a plurality of microstrip lines arranged equidistantly along the second direction;

[0026] A plurality of the microstrip lines are arranged to form a rectangular structure; wherein the second direction is perpendicular to the first direction.

[0027] Furthermore, the length of the microstrip line in the negative dielectric constant layer along the second direction is 1 / 6×λ, wherein λ is the wavelength of the electromagnetic wave.

[0028] Furthermore, the end projections of the negative dielectric constant layer coincide with the projections of the first opening and the second opening respectively.

[0029] The invention also discloses an electronic device which adopts the antenna structure.

[0030] Compared with the prior art, the present invention has at least the following beneficial effects:

[0031] By arranging the antenna radiation layer, negative magnetic permeability layer and negative dielectric constant layer on the top layer, middle layer and bottom layer of the support structure respectively, and making the positive projections of the negative magnetic permeability layer and the negative dielectric constant layer overlap in the first direction, a compact stacking layout and effective electromagnetic coupling of the three functional layers are achieved. This design enables the negative magnetic permeability layer and the negative dielectric constant layer to work synergistically to form double negative superconducting properties. At the same time, the antenna radiation layer improves the radiation performance through the strong coupling effect with the double negative superconducting properties, which not only significantly reduces the overall size of the antenna, but also improves the working efficiency of the antenna in multiple working frequency bands, providing a high-performance antenna solution for miniaturized communication equipment. BRIEF DESCRIPTION OF THE DRAWINGS

[0032] Figure 1 is a schematic structural diagram of the antenna structure in the present invention;

[0033] Figure 2 is another schematic diagram of the antenna structure of the present invention;

[0034] Figure 3 It is a schematic diagram of the structure of the antenna radiation layer in the present invention;

[0035] Figure 4 It is a schematic structural diagram of the negative magnetic permeability layer in the present invention;

[0036] Figure 5 is a schematic structural diagram of the negative dielectric constant layer in the present invention;

[0037] Figure 6 This is a graph showing the relationship between the effective dielectric constant of common structural materials and the frequency;

[0038] Figure 7 is a graph showing the relationship between the effective dielectric constant of the antenna of the present invention and the frequency;

[0039] Figure 8 is a graph showing the relationship between the relative magnetic permeability of the antenna and the frequency in the present invention;

[0040] Fig. 9is a graph showing the relationship between the refractive index of the antenna and the frequency in the present invention;

[0041] Fig.10 The curve diagram of the amplitude of the S parameter of the antenna in the present invention changing with the frequency

[0042] Fig.11 It is a curve showing that the total efficiency of the antenna in the present invention varies with frequency. DETAILED DESCRIPTION

[0043] The following will be described in more detail with reference to a schematic diagram of an antenna structure and an electronic device of the present invention, wherein a preferred embodiment of the present invention is shown. It should be understood that those skilled in the art can modify the present invention described herein while still achieving the advantageous effects of the present invention. Therefore, the following description should be understood as being widely known to those skilled in the art and not as a limitation of the present invention.

[0044] The present invention is described in more detail in the following paragraphs by way of example with reference to the accompanying drawings. The advantages and features of the present invention will become more apparent from the following description and claims. It should be noted that the drawings are in very simplified form and in non-precise proportions, and are only used to facilitate and clearly assist in illustrating the purpose of the embodiments of the present invention.

[0045] Please refer to Figure 1-Figure 5 This embodiment discloses an antenna structure, including: a support structure 5, an antenna radiation layer 1, a negative magnetic permeability layer 2 and a negative dielectric constant layer 3.

[0046] Specifically, the antenna radiation layer 1 , the negative magnetic permeability layer 2 and the negative dielectric constant layer 3 are respectively arranged on the top layer, the middle layer and the bottom layer of the support structure 5 .

[0047] The orthographic projection of the negative magnetic permeability layer 2 along the first direction partially overlaps with the orthographic projection of the negative dielectric constant layer 3 along the first direction, wherein the first direction (the Y direction shown in the figure) is the direction in which the antenna radiation layer 1 points to the negative dielectric constant layer 3.

[0048] In this embodiment, the antenna structure is suitable for multi-antenna operating frequency bands, such as: 2.4GHz (Wi-Fi, Bluetooth), 2.6GHz (4G LTE), 3.5GHz (5G mid-band), 5.8GH (Wi-Fi), 6GHz (Wi-Fi6E), 28GHz (5G millimeter wave), 39GHz (5G millimeter wave) and other communication frequency bands. Among them, the positive projections of the negative permeability layer 2 and the negative dielectric constant layer 3 in the first direction overlap, so that the negative permeability layer 2 and the negative dielectric constant layer 3 work together to form a double negative superconducting property, thereby forming a "left-handed propagation" characteristic, so that the electric field, magnetic field and wave vector form a left-handed propagation mode, which causes the phase velocity and group velocity to propagate in reverse, the wavelength is significantly shortened in the material, and the electromagnetic wave energy density is increased, which ultimately shortens the physical length of the electromagnetic wave of the same frequency in the double negative material, so that the same electrical length can be achieved using a smaller physical size, coupled with the enhanced near-field local effect and improved energy conversion efficiency of the double negative material, and finally achieves the miniaturization design goal of the antenna structure. At the same time, the antenna radiation layer 1 improves the radiation performance through the strong coupling effect with the double negative superconducting properties, further reducing the overall size of the antenna.

[0049] In this embodiment, the antenna radiation layer 1 includes a low-frequency arm and a high-frequency arm.

[0050] Specifically, the low-frequency arm half surrounds the high-frequency arm; one end of the low-frequency arm is connected to the antenna feeding point, and the other end forms an open circuit; one end of the high-frequency arm is connected to the antenna feeding point through the low-frequency arm, and the other end forms an open circuit.

[0051] In this embodiment, the layout of the low-frequency arm semi-surrounding the high-frequency arm realizes effective coupling of the electromagnetic field, so that the two radiating units are compactly integrated in space while maintaining electrical independent working capabilities; the design of connecting one end of the low-frequency arm to the feeding point and leaving the other end open forms a working mode similar to that of a dipole antenna, effectively radiating signals in the lower frequency band; the structure in which the high-frequency arm is indirectly connected to the feeding point through the low-frequency arm utilizes the principle of electromagnetic field coupling to generate strong resonance in the high frequency band; the reasonable setting of the open ends of the two radiating arms enables the antenna to have good impedance matching characteristics and reduces signal reflections.

[0052] Furthermore, in this embodiment, the length of the low frequency arm is 1 / 6×λ, and the length of the high frequency arm is 1 / 8×λ, where λ is the wavelength of the electromagnetic wave. For example, when the wavelength of the electromagnetic wave is 2.45 GHz, λ=c / f==3×10 8 m / s÷2.45×10 9 ≈12.24cm. Then the diameter of the microstrip line is 2.04cm. It is understandable that in different application scenarios, the operating frequency will be different, and the antenna arm length will be adjusted accordingly according to the above proportional relationship.

[0053] By selecting the above-mentioned low-frequency arm with a length of 1 / 6×λ and the high-frequency arm with a length of 1 / 8×λ, ideal resonant modes can be generated at multiple target frequencies.

[0054] In a specific embodiment, the low frequency arm includes a first antenna branch 101, a second antenna branch 102, a third antenna branch 103 and a fourth antenna branch 104. The high frequency arm includes a fifth antenna branch 105, a sixth antenna branch 106, a seventh antenna branch 107, an eighth antenna branch 108 and a ninth antenna branch 109.

[0055] Please refer to Figure 3 , the specific connection method is as follows: the first antenna branch 101, the second antenna branch 102 and the third antenna branch 103 are connected in sequence to form a low-frequency radiation section of a semi-enclosed rectangular frame structure; the fifth antenna branch 105, the sixth antenna branch 106 and the seventh antenna branch 107 are connected in sequence to form a high-frequency radiation section of a semi-enclosed rectangular frame structure;

[0056] The fourth antenna branch 104 is connected to one end of the low-frequency radiation segment, and the other end of the fourth antenna branch 104 is connected to the ninth antenna branch 109 of the high-frequency arm; one end of the ninth antenna branch 109 is connected to one end of the high-frequency radiation segment through the eighth antenna branch 108, and the other end is connected to the antenna feeding point.

[0057] The other ends of the low-frequency radiation section and the high-frequency radiation section are in an open circuit state.

[0058] The antenna radiation layer 1 adopts the above-mentioned connection structure, and the semi-enclosed rectangular structure of the low-frequency and high-frequency radiation segments realizes spatial folding and extends the electrical path; the fourth antenna branch 104 and the ninth antenna branch 109 serve as key connection branches to optimize the energy transfer between frequency bands; the open circuit design at the end of the radiation segment enhances the resonance effect; the overall structure not only realizes dual-band radiation and uniform directivity, but also can significantly reduce the size of the antenna.

[0059] Furthermore, in this embodiment, the design of the length of the antenna branch needs to take into account factors such as harmonic matching of the operating frequency, electromagnetic coupling effect, dual-band energy balance, and space folding efficiency.

[0060] In a specific embodiment, the length of the first antenna branch 101 is 4 mm, the length of the second antenna branch 102 is 9.7 mm, the length of the third antenna branch 103 is 6 mm, the length of the sixth antenna branch 106 is 5.3 mm, and the length of the ninth antenna branch 109 is 3.5 mm. The first antenna branch 101, the second antenna branch 102, the third antenna branch 103, the sixth antenna branch 106 and the ninth antenna are designed to have the above lengths so that the harmonic frequency of the antenna radiation layer 1 coincides with the working frequency band of 2.4 GHz, thereby forming an optimal resonance state.

[0061] Furthermore, in order to further adjust the resonant frequency of the antenna and optimize the frequency band coverage characteristics, this embodiment also provides tuning slots and resonance adjustment sections at key connections of the antenna radiation layer 1 .

[0062] Specifically, a tuning slot 113 is provided at the connection between the fifth antenna branch 105 and the sixth antenna branch 106; at least one resonance adjustment section is provided at the connection between the sixth antenna branch 106 and the seventh antenna branch 107, and at the connection between the seventh antenna branch 107 and the eighth antenna branch 108.

[0063] In a specific embodiment, a first resonance adjustment section 110 is provided at a connection between the sixth antenna branch 106 and the seventh antenna branch 107, close to the second antenna branch 103. A second resonance adjustment section 111 and a third resonance adjustment section 112 are provided at a connection between the seventh antenna branch 107 and the eighth antenna branch 108, close to the third antenna branch 103 and the fourth antenna branch 104, respectively.

[0064] Furthermore, in this embodiment, the negative magnetic permeability layer 2 includes a concentric double ring resonator (SSR).

[0065] Specifically, the concentric double ring resonator is a concentric double ring structure composed of an outer ring conductor 201 and an inner ring conductor 202, wherein: the outer ring conductor 201 is provided with a first opening 203 along the circumferential direction, and the inner ring conductor 202 is provided with a second opening 204 along the circumferential direction. The first opening 203 and the second opening 204 are located on opposite sides of the concentric double ring resonator.

[0066] In this embodiment, the diameter of the concentric double ring resonator is 1 / 10×λ, where λ is the wavelength of the electromagnetic wave. For example, when the wavelength of the electromagnetic wave is 2.45 GHz, λ=c / f==3×10 8 m / s÷2.45×10 9≈12.24cm. Then the diameter of the concentric double ring is 1.224cm. In different application scenarios, such as 900MHz, 2.45GHz, 5.8GHz and other communication frequency bands, the concentric double ring resonator can operate in different frequency ranges. Those skilled in the art can select a suitable operating frequency according to specific application requirements and adjust the diameter of the concentric double ring resonator accordingly.

[0067] The diameter of the concentric double ring resonator is designed to be 1 / 10×λ, so that the concentric double ring resonator can form a strong magnetic resonance response at the target frequency, thereby generating a stable negative magnetic permeability characteristic.

[0068] Furthermore, in this embodiment, the negative dielectric constant layer 3 includes a superconductor in a rectangular structure.

[0069] Specifically, the negative dielectric constant layer 3 includes a plurality of microstrip lines arranged equidistantly along a second direction. The second direction is perpendicular to the first direction. For example, the second direction may be a width direction or a length direction ( Figure 1 X direction as shown).

[0070] In this embodiment, the length of the microstrip line in the negative dielectric constant layer 3 along the second direction is 1 / 6×λ, where λ is the wavelength of the electromagnetic wave. For example, when the wavelength of the electromagnetic wave is 2.45 GHz, λ=c / f==3×10 8 m / s÷2.45×10 9 ≈12.24cm. Then the diameter of the microstrip line is 2.04cm. It is understandable that in different application scenarios, the negative dielectric constant layer 3 can operate in different frequency ranges, such as 900MHz, 2.45GHz, 5.8GHz and other communication frequency bands. Those skilled in the art can select a suitable operating frequency according to specific application requirements and adjust the length of the microstrip line accordingly.

[0071] Furthermore, the number and spacing of microstrip lines in the negative dielectric constant layer 3 are related to the operating frequency and the required negative dielectric constant value. In a specific embodiment, when the operating frequency is 2.4 GHz, 9 microstrip lines are selected, each microstrip line is 2.04 cm long (about 1 / 6 of the operating wavelength), the microstrip line width is 0.3 mm, and the spacing between adjacent microstrip lines is 1.2 mm, which can achieve an equivalent dielectric constant of about -2.7; and when the number of microstrip lines is reduced to 7 and the same spacing is maintained, the absolute value of the equivalent negative dielectric constant decreases by about 15%; when the microstrip line spacing is increased to 1.5 mm and 9 microstrip lines are maintained, the resonant frequency shifts to the low frequency direction by about 3%, and the absolute value of the negative dielectric constant decreases by about 12%; therefore, by adjusting the number and spacing of microstrip lines, the electromagnetic properties of the superconductor can be effectively regulated to adapt to different application scenarios.

[0072] Further, in this embodiment, along the second direction, the projection of the negative dielectric constant layer 3 coincides with the projection of the first opening 203 and the projection of the second opening 204. The coincidence in this embodiment means that when projecting in the second direction, the projection of the negative dielectric constant layer 3 corresponds exactly to the projection of the opening in the concentric double ring in spatial position. Such a design can form an effective electromagnetic coupling channel, thereby achieving the synergistic effect of negative dielectric and negative permeability properties, constructing a complete left-handed material property, and enhancing energy transmission efficiency, reducing parasitic radiation and loss.

[0073] Furthermore, the support structure 5 described in this embodiment is a substrate, and the antenna radiation layer 1, the negative magnetic permeability layer 2 and the negative dielectric constant layer 3 are respectively etched on the top layer, the middle layer and the bottom layer of the substrate through an etching process.

[0074] In a specific embodiment, the etching process may be wet etching, dry etching, laser direct imaging or other etching processes, which are not specifically limited herein.

[0075] In another specific embodiment, the material selection of the substrate includes but is not limited to epoxy glass fiber (FR-4) substrate, Rogers series high frequency board, polytetrafluoroethylene (PTFE) substrate, ceramic substrate, liquid crystal polymer substrate and other materials.

[0076] It is understandable that the dielectric properties of the substrate will affect the resonant frequency and bandwidth characteristics of the superconducting structure. Generally speaking, it is necessary to select a material with a smaller dielectric property to manufacture the substrate, because the smaller the dielectric property of the material, the smaller the impact on the resonant frequency and bandwidth characteristics of the superconducting structure. The preferred substrate material is epoxy glass fiber board (FR-4) as the substrate, which has a dielectric constant of about 4.2 and is well compatible with the double negative superconducting structure.

[0077] Please refer to Figure 6 , the parameters of common structural materials, dielectric constant Dk and magnetic permeability Df are all above 0, which means that the antenna only has conventional electromagnetic wave propagation characteristics. Please refer to Figure 7-Figure 9 , the antenna structure disclosed in this embodiment is used to successfully achieve a negative dielectric constant Er<0( Figure 7 shown) and negative magnetic permeability Mu<0( Figure 8 As shown), when these two parameters are negative at the same time, the refractive index n of the material also becomes negative at 2.4GHZ ( Fig. 9 As shown in the figure), the propagation characteristics of electromagnetic waves are changed, and the design goal of antenna miniaturization is further achieved. Figure 10-11 ,like Fig.10 The S11 return loss test results shown in the figure show that in the low frequency band, due to the special properties of the substrate (superconducting properties), some additional electromagnetic wave interference will be generated, but this does not affect the normal operation of the antenna. Fig.11 As shown, within the working frequency band of 2.4-2.5 GHz, the radiation efficiency of the antenna can reach more than 40%, meeting the requirements for use of daily electronic products.

[0078] The electronic device disclosed in this embodiment can be any of various types of computer system devices that are mobile or portable and perform wireless communication. Specifically, the electronic device can be a mobile phone or smart phone (e.g., a phone based on iPhone TM, a phone based on Android TM), a portable game device (e.g., Nintendo DS TM, PlayStationPortable TM, Gameboy Advance TM, iPhone TM), a laptop, a PDA, a portable Internet device, a music player, and a data storage device, other handheld devices, and headsets, etc. The electronic device can also be other wearable devices that need to be charged (e.g., a head-mounted device (HMD) such as an electronic bracelet, an electronic necklace, an electronic device, or a smart watch).

[0079] The electronic device can also be any one of a plurality of electronic devices, including but not limited to cellular phones, smart phones, other wireless communication devices, personal digital assistants, audio players, other media players, music recorders, video recorders, other media recorders, radios, medical devices, vehicle transportation instruments, calculators, programmable remote controls, pagers, laptop computers, desktop computers, printers, netbook computers, personal digital assistants (PDAs), portable multimedia players (PMPs), Moving Picture Experts Group (MPEG-1 or MPEGG-2) Audio Layer 3 (MP3) players, portable medical devices, and digital cameras and combinations thereof.

[0080] In some cases, the electronic device can perform multiple functions (e.g., play music, display video, store pictures, and receive and send phone calls). If desired, the electronic device can be a device such as a cellular phone, a media player, other handheld device, a wristwatch device, a pendant device, a handset device, or other compact portable device.

[0081] Obviously, those skilled in the art can make various changes and modifications to the present invention without departing from the spirit and scope of the present invention. Thus, if these modifications and variations of the present invention fall within the scope of the claims of the present invention and their equivalents, the present invention is also intended to include these modifications and variations.

Claims

1. An antenna structure, characterized in that: Includes: Support structure; an antenna radiation layer disposed on the top layer of the support structure; A negative magnetic permeability layer provided in the middle layer of the support structure; and, a negative dielectric constant layer disposed on the bottom layer of the support structure; The orthographic projection of the negative magnetic permeability layer along the first direction partially overlaps with the orthographic projection of the negative dielectric constant layer along the first direction, wherein the first direction is the direction from the antenna radiation layer to the negative dielectric constant layer.

2. The antenna structure according to claim 1, characterized in that: The antenna radiation layer includes a low-frequency arm and a high-frequency arm; The low frequency arm semi-surrounds the high frequency arm; One end of the low-frequency arm is connected to the antenna feeding point, and the other end is open; One end of the high-frequency arm is electrically connected to the antenna feeding point through the low-frequency arm, and the other end is open.

3. The antenna structure according to claim 2, characterized in that: The low frequency arm includes a first antenna branch, a second antenna branch, a third antenna branch and a fourth antenna branch. The high frequency arm includes a fifth antenna branch, a sixth antenna branch, a seventh antenna branch, an eighth antenna branch and a ninth antenna branch; The first antenna branch, the second antenna branch and the third antenna branch are connected in sequence to form a low-frequency radiation section with a semi-enclosed rectangular frame structure; The fifth antenna branch, the sixth antenna branch and the seventh antenna branch are connected in sequence to form a high-frequency radiation section with a semi-enclosed rectangular frame structure; The fourth antenna branch is connected to one end of the low-frequency radiation segment, and the other end of the fourth antenna branch is connected to the ninth antenna branch; One end of the ninth antenna branch is connected to one end of the high-frequency radiation section through the eighth antenna branch, and the other end is connected to the antenna feeding point; The other ends of the low-frequency radiation section and the high-frequency radiation section are in an open circuit state.

4. The antenna structure according to claim 3, characterized in that: A tuning slot is provided at the connection between the fifth antenna branch and the sixth antenna branch; The connection between the sixth antenna branch and the seventh antenna branch, and the connection between the seventh antenna branch and the eighth antenna branch are each provided with at least one resonance adjustment section.

5. The antenna structure according to claim 2, characterized in that: The negative magnetic permeability layer includes a concentric double ring resonator formed by an outer ring conductor surrounding an inner ring conductor; The outer ring conductor and the inner ring conductor are both composed of microstrip lines; The outer ring conductor is provided with a first opening along the circumferential direction, and the inner ring conductor is provided with a second opening along the circumferential direction; the first opening and the second opening are respectively located on two opposite sides of the concentric dual ring resonator.

6. The antenna structure according to claim 5, characterized in that: The diameter of the concentric double rings is 1 / 10×λ, where λ is the wavelength of the electromagnetic wave.

7. The antenna structure according to claim 5 or 6, characterized in that: The negative dielectric constant layer includes a plurality of microstrip lines arranged equidistantly along a second direction; the plurality of microstrip lines are arranged to form a rectangular structure; wherein the second direction is perpendicular to the first direction.

8. The antenna structure according to claim 7, characterized in that: The length of the microstrip line in the negative dielectric constant layer along the second direction is 1 / 6×λ, where λ is the wavelength of the electromagnetic wave.

9. The antenna structure according to claim 7, characterized in that: Along the second direction, the projection of the negative dielectric constant layer coincides with the projection of the first opening and the projection of the second opening.

10. An electronic device, characterized in that: The electronic device comprises the antenna structure according to any one of claims 1 to 9.

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