Energy feedback high power factor air conditioner compressor drive system

Abstract

The application belongs to the technical field of power electronics, and relates to an energy feedback high-power-factor air conditioner compressor driving system, which comprises a DC bus, DC bus electrolytic capacitors connected to the positive and negative poles of the DC bus respectively, a motor driving circuit and a shutdown energy feedback circuit with combined switching devices as bridge arms, a permanent magnet synchronous motor connected to the motor driving circuit, a motor control module for driving the combined switching devices in the motor driving circuit, an energy feedback control module for driving the combined switching devices in the shutdown energy feedback circuit, and the second connection end I of each phase bridge arm in the motor driving circuit and the shutdown energy feedback circuit is connected to the positive pole of the DC bus, and the second connection end II of each phase bridge arm is connected to the negative pole of the DC bus; the first connection end of the phase bridge arm of the shutdown energy feedback circuit is connected to the phase power grid voltage through a phase filter inductance. The application can maintain the stability of the DC bus voltage, and reduce the influence of power grid voltage fluctuation and air conditioner compressor load fluctuation.

Description

Technical Field

[0001] This invention belongs to the field of power electronics technology, and more specifically, relates to an energy feedback high power factor air conditioning compressor drive system. Background Technology

[0002] In air conditioning compressor drive systems with three-phase AC input, the traditional method of establishing the DC bus voltage is to use a three-phase uncontrolled rectifier bridge to obtain a DC bus that fluctuates with the grid voltage. In some regions, where grid voltage fluctuations are large, or even in scenarios where businesses are self-powered, the DC bus voltage of the uncontrolled rectifier fluctuates significantly, which can severely affect the control of the air conditioning compressor. Simultaneously, the uncontrolled rectifier has a low input current power factor and high current distortion rate, affecting the factory qualification of the air conditioning system. Furthermore, when the air conditioning compressor is running at high speed in a deep magnetic field weakening zone, a sudden stop can cause a surge in the DC bus voltage. Excessively high voltage can damage capacitors and power switching devices, affecting the safety and reliability of the entire air conditioning system.

[0003] In home appliances such as air conditioner compressor drive systems, the power switching devices used are mostly made of silicon (Si). Power switching devices made of Si have many drawbacks, such as: low withstand voltage, making them difficult to handle AC input voltage fluctuations and DC bus voltage surges caused by compressor shutdowns at high speeds; high switching losses, resulting in low overall efficiency of the air conditioner compressor drive system; and low switching frequency, which significantly limits performance under high-speed operating conditions, making the vibration and noise of the air conditioner compressor more noticeable. Summary of the Invention

[0004] This invention addresses the problems of low switching frequency and withstand voltage, and high switching losses in existing technologies by providing an energy feedback high power factor air conditioning compressor drive system that maintains the stability of the DC bus voltage and reduces the impact of grid voltage fluctuations and air conditioning compressor load fluctuations.

[0005] This invention provides an energy feedback high power factor air conditioner compressor drive system, comprising:

[0006] DC bus;

[0007] The motor drive circuit is a three-phase fully symmetrical bridge circuit composed of the combined switching devices as bridge arms. The second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus.

[0008] Permanent magnet synchronous motor, the permanent magnet synchronous motor of Compared with the motor drive circuit The first connecting end of the phase bridge arm is connected;

[0009] The motor control module is used to generate drive signals for the combined switching devices in the motor drive circuit;

[0010] A shutdown energy feedback circuit, wherein the shutdown energy feedback circuit is a three-phase fully symmetrical bridge circuit composed of the combined switching devices as bridge arms. The first connecting end of the phase bridge arm is through Phase filter inductor and Phase grid voltage connection, The second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus.

[0011] An energy feedback control module is used to generate drive signals for the combined switching devices in the shutdown energy feedback circuit;

[0012] DC bus electrolytic capacitor C dc The DC bus electrolytic capacitor is connected between the shutdown energy feedback circuit and the motor drive circuit. C dc The two ends are connected to the positive and negative terminals of the DC bus, respectively.

[0013] In some embodiments, the combined switching device includes:

[0014] First connection end;

[0015] The second connection end includes a second connection end I and a second connection end II;

[0016] An inductor assembly includes inductor I and inductor II, wherein the first end of inductor I and the first end of inductor II are both connected to the first connection terminal;

[0017] Switching circuit I, including diode I and... SiC-Mos Pipe I and SiC-Mos The first series circuit formed by connecting tubes II in series; SiC-Mos Source connection of tube I SiC-Mos The drain of tube II, SiC-Mos The drain of tube I is connected to the second connection terminal I; SiC- Mos The source of diode II is connected to the cathode of diode I. SiC-Mos The connection point between the source of diode II and the cathode of diode I is connected to the second terminal of inductor II, and the anode of diode I is connected to the second connection terminal II;

[0018] Switching circuit II, including diode II and... SiC-Mos Pipe III and SiC-Mos A second series circuit formed by connecting tubes IV in series; SiC-Mos Source connection of tube IIISiC-Mos The drain of tube IV, SiC-Mos The drain of diode III is connected to the anode of diode II. SiC-Mos The connection point between the drain of diode III and the anode of diode II is connected to the second terminal of inductor I; the cathode of diode II is connected to the second connection terminal I. SiC-Mos The source of tube IV is connected to the second connection terminal II.

[0019] In some embodiments, the motor control module includes:

[0020] dq The axis reference voltage setpoint module obtains the value based on the system running time and switching time. d The actual rise slope of the shaft reference voltage Regarding the above d The actual rise slope of the shaft reference voltage After integration and amplitude limiting, the result is obtained d Shaft reference voltage setpoint , and given q Shaft reference voltage setpoint The value of is always 0;

[0021] The angle setting module provides a ramp-up value for the reference setpoint rotational speed. n ramp The actual reference speed setpoint is obtained by limiting the amplitude. n ref Based on the actual reference speed set value n ref Calculate the reference setpoint for the electrical angle. ω eref For electrical angle reference setpoint ω eref Integrating the results yields the operating electrical angle of the air conditioner compressor. θ m Regarding the electrical angle θ m Perform trigonometric operations to obtain the sine value of the angle corresponding to the rotating coordinate system of the air conditioner compressor. θ m And cosine value cos θ m ;

[0022] Two-phase voltage modulation wave conversion module I, will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ;

[0023] Three-phase voltage modulation wave conversion module I converts the two-phase stationary coordinate system... α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system;

[0024] Sine modulation module I performs per-unit processing on the three-phase voltage modulation wave to obtain the per-unitized three-phase voltage modulation wave. Based on the per-unitized three-phase voltage modulation wave and the triangular carrier wave... Z m The magnitude comparison generates the drive signal for the combined switching device in the motor drive circuit.

[0025] In some embodiments, the two-phase voltage modulation wave conversion module I will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows:

[0026] d Shaft reference voltage setpoint cos θ m Obtain intermediate variables v mαp1 , q Shaft reference voltage setpoint Multiply by sin θ m Obtain intermediate variables v mαp2 intermediate variables v mαp1 Subtract intermediate variables v mαp2 get α Axis voltage modulated wave ;

[0027] d Shaft reference voltage setpoint Multiply by sin θ m Obtain intermediate variables v mβp1 , q Shaft reference voltage setpoint cos θ m Obtain intermediate variables v mβp2 intermediate variables vmβp1 Add intermediate variables v mβp2 get β Axis voltage modulated wave .

[0028] In some embodiments, the three-phase voltage modulation wave conversion module I will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows:

[0029] a Phase voltage modulation wave equal α Axis voltage modulated wave ;

[0030] α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. v tempα1 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ1 ;

[0031] intermediate variables v tempβ1 Subtract intermediate variables v tempα1 ,get b Phase voltage modulation wave ;

[0032] intermediate variables v tempα1 Subtract the intermediate variable after taking the negative value v tempβ1 ,get c Phase voltage modulation wave .

[0033] In some embodiments, the sinusoidal modulation module I modulates the three-phase voltage modulation wave after standardization with a triangular carrier wave. Z m The method for generating the drive signal for the combined switching device in the motor drive circuit by comparing the magnitudes is as follows:

[0034] The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z m Size;

[0035] like Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Pipe I S mi1 PWM drive signal mi1 and SiC-Mos Pipe II S mi2 PWM drive signal mi2 The high level is obtained by negating the high level using NOT. SiC-Mos Pipe III S mi3 PWM drive signal mi3 and SiC-Mos Pipe IV S mi4 PWM drive signal mi4 Low level;

[0036] like Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. SiC-Mos Pipe I S mi1 PWM drive signal mi1 and SiC-Mos Pipe II S mi2 PWM drive signal mi2 The low level is obtained by negating the low level using NOT. SiC-Mos Pipe III S mi3 PWM drive signal mi3 and SiC-Mos Pipe IV S mi4 PWM drive signal mi4 It is a high level.

[0037] In some embodiments, the drive system further includes an energy feedback control module, the energy feedback control module comprising:

[0038] Two-phase voltage modulation waveform conversion module II converts the shutdown energy feedback circuit in a rotating coordinate system. d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ;

[0039] Three-phase voltage modulation wave conversion module II converts the two-phase stationary coordinate system... α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system;

[0040] Sine modulation module II performs per-unit processing on the three-phase voltage modulation wave to obtain the per-unitized three-phase voltage modulation wave. Based on the per-unitized three-phase voltage modulation wave and the triangular carrier wave... Z g The magnitude comparison generates the drive signal for the combined switching device in the shutdown energy feedback circuit.

[0041] In some embodiments, the two-phase voltage modulation wave conversion module II will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows:

[0042] d Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gαp1 , q Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gαp2 intermediate variables v gαp1 Subtract intermediate variables v gαp2 get α Axis voltage modulated wave ,in, θ g The angle corresponding to the rotating coordinate system of the shutdown energy feedback circuit;

[0043] d Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gβp1 , q Shaft reference voltage setpoint cos θ g Obtain intermediate variablesv gβp2 intermediate variables v gβp1 Add intermediate variables v gβp2 get β Axis voltage modulated wave .

[0044] In some embodiments, the three-phase voltage modulation wave conversion module II will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows:

[0045] a Phase voltage modulation wave equal α Axis voltage modulated wave ;

[0046] α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. v tempα2 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ2 ;

[0047] intermediate variables v tempβ2 Subtract intermediate variables v tempα2 ,get b Phase voltage modulation wave ;

[0048] intermediate variables v tempα2 Subtract the intermediate variable after taking the negative value v tempβ2 ,get c Phase voltage modulation wave .

[0049] In some embodiments, the sinusoidal modulation module II modulates the three-phase voltage modulation wave after standardization with a triangular carrier wave. Z g The method for generating the drive signal for the combined switching device in the shutdown energy feedback circuit by comparing the magnitudes is as follows:

[0050] The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z g Size;

[0051] like Phase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. SiC-Mos Pipe I S gi1 PWM drive signal gi1 and SiC-Mos Pipe II S gi2 PWM drive signal gi2 The high level is obtained by negating the high level using NOT. SiC-Mos Pipe III S gi3 PWM drive signal gi3 and SiC-Mos Pipe IV S gi4 PWM drive signal gi4 Low level;

[0052] like Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Pipe I S gi1 PWM drive signal gi1 and SiC-Mos Pipe II S gi2 PWM drive signal gi2 The low level is obtained by negating the low level using NOT. SiC-Mos Pipe III S gi3 PWM drive signal gi3 and SiC-Mos Pipe IV S gi4 PWM drive signal gi4 It is a high level.

[0053] Compared with the prior art, the advantages and positive effects of the present invention are as follows:

[0054] (1) The energy feedback high power factor air conditioner compressor drive system provided by the present invention is equipped with a shutdown energy feedback circuit. Through the shutdown energy feedback circuit, the energy of DC bus voltage pumping caused by the air conditioner compressor deceleration and high speed operation is fed to the power grid, maintaining the stability of DC bus voltage, reducing the impact of power grid voltage fluctuation and air conditioner compressor load fluctuation, protecting DC bus electrolytic capacitor and power devices, improving the stability and reliability of air conditioner compressor drive system, and at the same time, energy feedback can also achieve the purpose of energy saving and consumption reduction.

[0055] (2) The energy feedback high power factor air conditioning compressor drive system provided by the present invention uses a combination switching device in both the motor drive circuit and the shutdown energy feedback circuit. The combination switching device is provided with two parallel switching circuits. In each switching circuit, two SiC-Mos After the transistors are connected in series to form a series circuit, they are connected in series with a diode. The series connection scheme can improve the overall withstand voltage of the combined switching device, increase the circuit reliability of the combined switching device, reduce the mutual interference between the two switching circuits by adding two inductors, achieve high switching frequency and high withstand voltage, reduce switching losses, stabilize DC bus voltage, reduce the impact of grid voltage fluctuations, and improve the stability and reliability of the air conditioning compressor drive system.

[0056] (3) The energy feedback high power factor air conditioner compressor drive system provided by the present invention can actively perform power factor correction through the motor control module and the energy feedback control module, effectively reducing the input current distortion rate and improving the sinusoidal nature of the input current. Attached Figure Description

[0057] Figure 1 This is a circuit diagram of the energy feedback high power factor air conditioner compressor drive system described in an embodiment of the present invention;

[0058] Figure 2 This is a circuit diagram of the combined switching device described in an embodiment of the present invention;

[0059] Figure 3 In this embodiment of the invention, the output current of the motor control circuit is positive and SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Conductive, SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When shut down a Phase bridge arm X a A schematic diagram of the current flow direction;

[0060] Figure 4 In this embodiment of the invention, the output current of the motor control circuit is positive and SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Shut down SiC-Mos Tube S ma3 and SiC-Mos TubeS ma4 When conducting a Phase bridge arm X a A schematic diagram of the current flow direction;

[0061] Figure 5 In this embodiment of the invention, the output current of the motor control circuit is negative and SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Conductive, Si-Mos Tube SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When shut down a Phase bridge arm X a A schematic diagram of the current flow direction;

[0062] Figure 6 In this embodiment of the invention, the output current of the motor control circuit is negative and SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Shut down SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When conducting a Phase bridge arm X a A schematic diagram of the current flow direction;

[0063] Figure 7 In this embodiment of the invention, the output current of the shutdown energy feedback circuit is positive and SiC-Mos Tube S ga1 and SiC- Mos Tube S ga2 Conductive, SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When shut down a Phase bridge arm Y a A schematic diagram of the current flow direction;

[0064] Figure 8In this embodiment of the invention, the output current of the shutdown energy feedback circuit is positive and SiC-Mos Tube S ga1 and SiC- Mos Tube S ga2 Shut down SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When conducting a Phase bridge arm Y a A schematic diagram of the current flow direction;

[0065] Figure 9 In this embodiment of the invention, the output current of the shutdown energy feedback circuit is negative and SiC-Mos Tube S ga1 and SiC- Mos Tube S ga2 Conductive, SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When shut down a Phase bridge arm Y a A schematic diagram of the current flow direction;

[0066] Figure 10 In this embodiment of the invention, the output current of the shutdown energy feedback circuit is negative and SiC-Mos Tube S ga1 and SiC- Mos Tube S ga2 Shut down SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When conducting a Phase bridge arm Y a A schematic diagram of the current flow direction;

[0067] Figure 11 As described in the embodiments of the present invention dq Schematic diagram of the axis reference voltage setting module;

[0068] Figure 12 This is a schematic diagram of the angle setting module described in an embodiment of the present invention;

[0069] Figure 13 This is a schematic diagram of the two-phase voltage modulation wave conversion module I described in an embodiment of the present invention;

[0070] Figure 14 This is a schematic diagram of the three-phase voltage modulation wave conversion module I according to an embodiment of the present invention;

[0071] Figure 15 This is a schematic diagram of the sinusoidal modulation module I described in an embodiment of the present invention;

[0072] Figure 16 This is a schematic diagram of the two-phase voltage modulation wave conversion module II described in an embodiment of the present invention;

[0073] [[ID=1 This is a schematic diagram of the three-phase voltage modulation wave conversion module II according to an embodiment of the present invention;

[0074] ​ This is a schematic diagram of the sinusoidal modulation module II described in an embodiment of the present invention;

[0075] ​ For existing traditional air conditioning compressor drive systems a Schematic diagram of phase grid voltage and current waveforms;

[0076] ​ A schematic diagram of the DC bus voltage waveform of a conventional air conditioner compressor drive system;

[0077] ​ The energy feedback high power factor air conditioning compressor drive system described in this embodiment of the invention a Schematic diagram of phase grid voltage and current waveforms;

[0078] ​ This is a schematic diagram of the DC bus voltage waveform of the energy feedback high power factor air conditioner compressor drive system according to an embodiment of the present invention.

[0079] In the diagram, 101 is the first connection terminal, 102 is the second connection terminal I, 103 is the second connection terminal II, 200 is the DC bus, 300 is the motor drive circuit, 400 is the shutdown energy feedback circuit, 500 is the motor control module, and 501 is... ​ Shaft reference voltage setting module, 502; Angle setting module, 503; Two-phase voltage modulation wave transformation module I, 504; Three-phase voltage modulation wave transformation module I, 505; Sine modulation module I, 600; Energy feedback control module, 601; Two-phase voltage modulation wave transformation module II, 602; Three-phase voltage modulation wave transformation module II, 603; Sine modulation module II. Detailed Implementation

[0080] The present invention will now be described in detail with reference to the accompanying drawings through exemplary embodiments. However, it should be understood that, without further description, elements, structures, and features in one embodiment may be advantageously incorporated into other embodiments.

[0081] In the home appliance industry, existing air conditioner compressor drive systems mostly use silicon (Si) materials for their power switching devices. However, Si-based power switching devices suffer from low voltage withstand and switching frequency, high switching losses, and are unable to stabilize AC input voltage fluctuations and DC bus voltage fluctuations. This invention provides an energy-recovery high power factor air conditioner compressor drive system with a shutdown energy feedback circuit. This circuit feeds the energy generated by the air conditioner compressor slowing down or stopping at high speeds back to the power grid, maintaining DC bus voltage stability, reducing the impact of grid voltage fluctuations and air conditioner compressor load fluctuations, protecting the DC bus electrolytic capacitors and power devices, and improving the stability and reliability of the air conditioner compressor drive system. Simultaneously, energy feedback also achieves energy saving and consumption reduction.

[0082] The energy feedback high power factor air conditioning compressor drive system of the present invention will be described in detail below with reference to the accompanying drawings and embodiments.

[0083] See ​ This invention provides an energy-feedback high power factor air conditioner compressor drive system, the drive system including a DC bus 200 and a DC bus electrolytic capacitor. C dc The system comprises a motor drive circuit 300, a shutdown energy feedback circuit 400, a permanent magnet synchronous motor M, a motor control module 500, and an energy feedback control module 600. The three-phase grid voltage is converted to DC voltage by the shutdown energy feedback circuit 400, and then inverted into three-phase AC voltage by the motor drive circuit 300, which is output to the permanent magnet synchronous motor M to drive its rotation, thereby driving the air conditioner compressor. When the air conditioner compressor decelerates or brakes and stops, it generates energy, which is then fed back to the DC bus 200. The shutdown energy feedback circuit 400 feeds excess energy back to the three-phase grid, preventing damage to the drive system caused by the energy generated by the air conditioner compressor. An electrolytic capacitor is also included on the DC bus. C dc The DC bus electrolytic capacitor is connected between the shutdown energy feedback circuit and the motor drive circuit. C dcThe two ends are respectively connected to the positive and negative terminals of the DC bus to stabilize the DC bus voltage. The motor drive circuit 300 is a three-phase fully symmetrical bridge circuit composed of combined switching devices as bridge arms. In the motor drive circuit 300, the second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus 200, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus 200. The permanent magnet synchronous motor M... Compared with the motor drive circuit 300 The first connecting end of the phase bridge arm is connected. The motor control module 500 is used to generate drive signals for the combined switching devices in the motor drive circuit 300. The shutdown energy feedback circuit 400 is a three-phase fully symmetrical bridge circuit composed of combined switching devices as bridge arms. The first connecting end of the phase bridge arm is through Phase filter inductor and The phases are connected to the grid voltage. The second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus 200, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus 200. The energy feedback control module 600 is used to generate drive signals for the combined switching devices in the shutdown energy feedback circuit 400.

[0084] Specifically, through a large-capacity (e.g., 1000uF) DC bus electrolytic capacitor. C dc Maintain the stability of the bus voltage.

[0085] See ​ The combined switching device includes:

[0086] First connection terminal 101;

[0087] The second connection end includes a second connection end I102 and a second connection end II103;

[0088] Inductor components, including inductors L 1 and inductor L 2. Inductance L The first terminal of 1 and the inductor L The first ends of 2 are all connected to the first connection end 101;

[0089] Switching circuit I, including diodes D 1 and by ​ Tube S 1 and ​ Tube S 2. A series circuit formed by connecting two series components; ​ Tube S 1 source connection ​ Tube S 2's drain, ​ Tube SThe drain of 1 is connected to the second connection terminal I102; ​ Tube S 2 source-connected diode D Cathode 1, ​ Tube S 2 source and diode D The cathode connection point of 1 and the inductor L The second end of 2 is connected; diode D The anode of 1 is connected to the second connection terminal II103;

[0090] Switching circuit II, including diodes D 2 and by ​ Tube S 3 and ​ Tube S 4. Series circuit formed by connecting series; ​ Tube S 3 source connection ​ Tube S 4 drain, ​ Tube S 3. Drain-connected diode D The anode of 2, ​ Tube S 3's drain and diode D The connection point of the anode of 2 with the inductor L The second terminal of 1 is connected; diode. D The cathode of 2 is connected to the second connection terminal I102. ​ Tube S The source of 4 is connected to the second connection terminal II103.

[0091] The embodiments of the present invention describe a design of two parallel switching circuits in a combined switching device, each circuit comprising two... ​ A tube and a diode, two ​ The transistors are connected in series to form a series circuit. ​ The use of tubes and series connection schemes can improve the overall withstand voltage and switching speed of combination switching devices, reduce switching losses, and increase the circuit reliability of combination switching devices. By adding two inductors, the mutual interference between the two switching circuits can be reduced, thereby increasing the reliability of the circuit.

[0092] See also ​ In the motor drive circuit 300, a Phase bridge arm X a Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L ma1 and inductor L ma2 Switching circuit I includes ​ TubeS ma1 , ​ Tube S ma2 and diodes D ma1 Switching circuit II includes ​ Tube S ma3 , ​ Tube S ma4 and diodes D ma2 . ​ Tube S ma1 source connection ​ Tube S ma2 The drain electrode, ​ Tube S ma1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. ​ Tube S ma2 Source-connected diode D ma1 The cathode, ​ Tube S ma2 source and diode D ma1 Cathode connection point X ma2 With inductance L ma2 Connection. Diode. D ma1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. ​ Tube S ma3 source connection ​ Tube S ma4 The drain electrode, ​ Tube S ma3 Drain-connected diode D ma2 anode, ​ Tube S ma3 Drain and diode D ma2 anode connection point X ma1 With inductance L ma1 The second end is connected. Diode. D ma2The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. ​ Tube S ma4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L ma1 and inductor L ma2 The first end is connected to point X ma ,point X ma Connected to the first connection end, the first connection end is connected to the permanent magnet synchronous motor M. a Connected to each other, for permanent magnet synchronous motor M a Provide a Phase voltage u ma .

[0093] b Phase bridge arm X b Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L mb1 and inductor L mb2 Switching circuit I includes ​ Tube S mb1 , ​ Tube S mb2 and diodes D mb1 Switching circuit II includes ​ Tube S mb3 , ​ Tube S mb4 and diodes D mb2 . ​ Tube S mb1 source connection ​ Tube S mb2 The drain electrode, ​ Tube S mb1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. ​ Tube S mb2 Source-connected diode I D mb1 The cathode, ​ Tube S mb2source and diode D mb1 Cathode connection point X mb2 With Inductor II L mb2 Connection. Diode. D mb1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. ​ Tube S mb3 source connection ​ Tube S mb4 The drain electrode, ​ Tube S mb3 Drain-connected diode D mb2 anode, ​ Tube S mb3 Drain and diode D mb2 anode connection point X mb1 With inductance L mb1 The second end is connected. Diode. D mb2 The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. ​ Tube S mb4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L mb1 and inductor L mb2 The first end is connected to point X mb ,point X mb Connected to the first connection end, the first connection end is connected to the permanent magnet synchronous motor M. b Connected to each other, for permanent magnet synchronous motor M b Provide b Phase voltage u mb .

[0094] c Phase bridge arm X c Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L mc1 and inductor L mc2 Switching circuit I includes ​ TubeS mc1 , ​ Tube S mc2 and diodes D mc1 Switching circuit II includes ​ Tube S mc3 , ​ Tube S mc4 and diodes D mc2 . ​ Tube S mc1 source connection ​ Tube S mc2 The drain electrode, ​ Tube S mc1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. ​ Tube S mc2 Source-connected diode D mc1 The cathode, ​ Tube S mc2 source and diode D mc1 Cathode connection point X mc2 With inductance L mc2 Connection. Diode. D mc1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. ​ Tube S mc3 source connection ​ Tube S mc4 The drain electrode, ​ Tube S mc3 Drain-connected diode D mc2 anode, ​ Tube S mc3 Drain and diode D mc2 anode connection point X mc1 With inductance L mc1 The second end is connected. Diode. D mc2The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. ​ Tube S mc4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L mc1 and inductor L mc2 The first end is connected to point X mc ,point X mc Connected to the first connection end, the first connection end is connected to the permanent magnet synchronous motor M. c Connected to each other, for permanent magnet synchronous motor M c Provide c Phase voltage u mc .

[0095] When the motor control circuit is working, the output current of the motor control circuit is alternating current. Therefore, there are four switching states for each phase bridge arm in the motor control circuit, which are described below. a Phase bridge arm X a Let's take an example to illustrate.

[0096] a Phase bridge arm X a The first connection terminal is connected to the permanent magnet synchronous motor M. a Connected, a Phase bridge arm X a The second connection terminal I is connected to the positive terminal of the DC bus. a Phase bridge arm X a The second connection terminal II is connected to the negative terminal of the DC bus.

[0097] When the output current of the motor control circuit is positive, that is, current flows out... a Phase bridge arm X a hour:

[0098] See ​ ,when ​ Tube S ma1 and ​ Tube S ma2 Conduction (i.e.) ​ Tube S ma1 and ​ Tube S ma2 The drive signal is high level. ​ TubeS ma3 and ​ Tube S ma4 Shutdown (i.e.) ​ Tube S ma3 and SiC-Mos Tube S ma4 When the drive signal is low, a Phase bridge arm X a The current is from SiC-Mos Tube S ma1 Flow direction SiC-Mos Tube S ma2 ,inductance L ma2 At this time, the current flows from the positive terminal of the DC bus to... X ma Points, Explanation X ma The potential at the point is lower than that at the positive terminal of the DC bus. This is due to the diode. D ma2 anode connection point X ma1 pass L ma1 and X ma Point connection, and diode D ma2 If the cathode of the diode is connected to the positive terminal of the DC bus, then the diode... D ma2 The anode voltage is lower than that of the diode. D ma2 The cathode voltage, thereby causing the diode D ma2 The diode will not conduct under reverse voltage, and no current will flow through it. D ma2 Due to diodes D ma1 cathode connection point X ma2 pass SiC-Mos Tube S ma2 and SiC- Mos Tube S ma1 The diode is connected to the positive terminal of the DC bus. D ma1 If the anode of the diode is connected to the negative terminal of the DC bus, then the diode... D ma1 The anode voltage is lower than that of the diode. D ma1The cathode voltage, thereby causing the diode D ma1 The diode will not conduct under reverse voltage, and no current will flow through it. D ma1 .

[0099] See Figure 4 ,when SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Shutdown (i.e.) SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 The drive signal is low level. SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 Conduction (i.e.) SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When the drive signal is high, due to the diode D ma1 The single-transistor voltage drop makes it easier for current to flow through the diode. D ma1 And flow in the opposite direction SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 The current is very small and negligible, therefore a Phase bridge arm X a The current is mainly supplied by the diode. D ma1 Flow to inductor L ma2 .

[0100] When the output current of the motor control circuit is negative, that is, when current flows in... a Phase bridge arm X a hour:

[0101] See Figure 5 ,when SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Conduction (i.e.) SiC-Mos TubeS ma1 and SiC-Mos Tube S ma2 The drive signal is high level. SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 Shutdown (i.e.) SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When the drive signal is low, due to the diode D ma2 The single-transistor voltage drop makes it easier for current to flow through the diode. D ma2 And flow in the opposite direction SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 The current is very small and negligible. a Phase bridge arm X a The current is mainly generated by the inductance. L ma1 Flow diode D ma2 .

[0102] See Figure 6 ,when SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Shutdown (i.e.) SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 The drive signal is low level. SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 Conduction (i.e.) SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When the drive signal is high, a Phase bridge arm X a The current is supplied by the inductor Lma1 Flow direction SiC-Mos Tube S ma3 , SiC-Mos Tube S ma4 At this time, the current is from X ma The point flows to the negative terminal of the DC bus, indicating that... X ma The potential at the point is higher than that at the negative terminal of the DC bus. This is due to the diode. D ma1 cathode connection point X ma2 Through inductance L ma2 and X ma Point connection, and diode D ma1 If the anode of the diode is connected to the negative terminal of the DC bus, then the diode... D ma1 The anode voltage is lower than that of the diode. D ma1 The cathode voltage, thereby causing the diode D ma1 The diode will not conduct under reverse voltage, and no current will flow through it. D ma1 Due to diodes D ma2 The cathode is connected to the positive terminal of the DC bus, and the diode... D ma2 anode connection point X ma1 pass SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When connected to the negative terminal of the DC bus, the diode... D ma2 The anode voltage is lower than that of the diode. D ma2 The cathode voltage, thereby causing the diode D ma2 The diode will not conduct under reverse voltage, and no current will flow through it. D ma2 .

[0103] In the motor control circuit, the switching transistors of each phase bridge arm are turned on or off by the drive signals generated by the motor control module.

[0104] In the shutdown energy feedback circuit 400, a Phase bridge arm Y aIncludes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L ga1 and inductor L ga2 Switching circuit I includes SiC-Mos Tube S ga1 , SiC-Mos Tube S ga2 and diodes D ga1 Switching circuit II includes SiC-Mos Tube S ga3 , SiC-Mos Tube S ga4 and diodes D ga2 . SiC-Mos Tube S ga1 source connection SiC-Mos Tube S ga2 The drain electrode, SiC-Mos Tube S ga1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S ga2 Source-connected diode D ga1 The cathode, SiC-Mos Tube S ga2 source and diode D ga1 Cathode connection point X ga2 With inductance L ga2 Connection. Diode. D ga1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. SiC-Mos Tube S ga3 source connection SiC-Mos Tube S ga4 The drain electrode, SiC-Mos Tube S ga3 Drain-connected diode D ga2 anode, SiC-Mos Tube S ga3 Drain and diode D ga2anode connection point X ga1 With inductance L ga1 The second end is connected; diode D ga2 The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S ga4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L ga1 and inductor L ga2 The first end is connected to point X ga ,point X ga Connected to the first connection end, the first connection end through a Phase filter inductor L a connect a Phase grid voltage u ga .

[0105] b Phase bridge arm Y b Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L gb1 and inductor L gb2 Switching circuit I includes SiC-Mos Tube S gb1 , SiC-Mos Tube S gb2 and diodes D gb1 Switching circuit II includes SiC-Mos Tube S gb3 , SiC-Mos Tube S gb4 and diodes D gb2 . SiC-Mos Tube S gb1 source connection SiC-Mos Tube S gb2 The drain electrode, SiC-Mos Tube S gb1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube Sgb2 Source-connected diode D gb1 The cathode, SiC-Mos Tube S gb2 source and diode D gb1 Cathode connection point X gb2 With inductance L gb2 Connection. Diode. D gb1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. SiC-Mos Tube S gb3 source connection SiC-Mos Tube S gb4 The drain electrode, SiC-Mos Tube S gb3 Drain-connected diode D gb2 anode, SiC-Mos Tube S gb3 Drain and diode D gb2 anode connection point X gb1 With inductance L gb1 The second end is connected; diode D gb2 The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S gb4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L gb1 and inductor L gb2 The first end is connected to point X gb ,point X gb Connected to the first connection end, the first connection end through b Phase filter inductor L b connect b Phase grid voltage u gb .

[0106] c Phase bridge arm Y cIncludes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L gc1 and inductor L gc2 Switching circuit I includes SiC-Mos Tube S gc1 , SiC-Mos Tube S gc2 and diodes D gc1 Switching circuit II includes SiC-Mos Tube S gc3 , SiC-Mos Tube S gc4 and diodes D gc2 . SiC-Mos Tube S gc1 source connection SiC-Mos Tube S gc2 The drain electrode, SiC-Mos Tube S gc1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S gc2 Source-connected diode D gc1 The cathode, SiC-Mos Tube S gc2 source and diode D gc1 Cathode connection point X gc2 With inductance L gc2 Connection. Diode. D gc1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. SiC-Mos Tube S gc3 source connection SiC-Mos Tube S gc4 The drain electrode, SiC-Mos Tube S gc3 Drain-connected diode D gc2 anode, SiC-Mos Tube S gc3 Drain and diode D gc2anode connection point X gc1 With inductance L gc1 The second end is connected; diode D gc2 The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S gc4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L gc1 and inductor L gc2 The first end is connected to point X gc ,point X gc Connected to the first connection end, the first connection end through c Phase filter inductor L c connect c Phase grid voltage u gc .

[0107] When the shutdown energy feedback circuit is in operation, the output current of the circuit is alternating current. Therefore, there are four switching states for each phase arm of the shutdown energy feedback circuit, which are described below. a Phase bridge arm Y a Let's take an example to illustrate.

[0108] a Phase bridge arm Y a The first connection end is through a Phase filter inductor L a connect a Phase grid voltage u ga , a Phase bridge arm Y a The second connection terminal I is connected to the positive terminal of the DC bus. a Phase bridge arm Y a The second connection terminal II is connected to the negative terminal of the DC bus.

[0109] When the output current of the shutdown energy feedback circuit is positive, that is, current flows out... a Phase bridge arm Y a hour:

[0110] See Figure 7 ,when SiC-Mos Tube Sga1 and SiC-Mos Tube S ga2 Conduction (i.e.) SiC-Mos Tube S ga1 and SiC-Mos Tube S ga2 The drive signal is high level. SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 Shutdown (i.e.) SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When the drive signal is low, a Phase bridge arm Y a The current is from SiC-Mos Tube S ga1 Flow direction SiC-Mos Tube S ga2 ,inductance L ga2 At this time, the current flows from the positive terminal of the DC bus to... X ga Points, Explanation X ga The potential at the point is lower than that at the positive terminal of the DC bus. This is due to the diode. D ga2 anode connection point X ga1 Through inductance L ga1 and X ga Point connection, and diode D ga2 If the cathode of the diode is connected to the positive terminal of the DC bus, then the diode... D ga2 The anode voltage is lower than that of the diode. D ga2 The cathode voltage, thereby causing the diode D ga2 The diode will not conduct under reverse voltage, and no current will flow through it. D ga2 Due to diodes D ga1 cathode connection point X ga2 pass SiC-Mos Tube S ga2 andSiC-Mos Tube S ga1 The diode is connected to the positive terminal of the DC bus. D ga1 If the anode of the diode is connected to the negative terminal of the DC bus, then the diode... D ga1 The anode voltage is lower than that of the diode. D ga1 The cathode voltage, thereby causing the diode D ga1 The diode will not conduct under reverse voltage, and no current will flow through it. D ga1 .

[0111] See Figure 8 ,when SiC-Mos Tube S ga1 and SiC-Mos Tube S ga2 Shutdown (i.e.) SiC-Mos Tube S ga1 and SiC-Mos Tube S ga2 The drive signal is low level. SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 Conduction (i.e.) SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When the drive signal is high, due to the diode D ga1 The single-transistor voltage drop makes it easier for current to flow through the diode. D ga1 And flow in the opposite direction SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 The current is very small and negligible, therefore a Phase bridge arm Y a The current is mainly supplied by the diode. D ga1 Flow to inductor L ga2 .

[0112] When the output current of the shutdown energy feedback circuit is negative, that is, current flows into... a Phase bridge arm Ya hour:

[0113] See Figure 9 ,when SiC-Mos Tube S ga1 and SiC-Mos Tube S ga2 Conduction (i.e.) SiC-Mos Tube S ga1 and SiC-Mos Tube S ga2 The drive signal is high level. SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 Shutdown (i.e.) SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When the drive signal is low, due to the diode D ga2 The single-transistor voltage drop makes it easier for current to flow through the diode. D ga2 And flow in the opposite direction SiC-Mos Tube S ga1 and SiC-Mos Tube S ga2 The current is very small and negligible. a Phase bridge arm Y a The current is mainly generated by the inductance. L ga1 Flow diode D ga2 .

[0114] See Figure 10 ,when SiC-Mos Tube S ga1 and SiC-Mos Tube S ga2 Shutdown (i.e.) SiC-Mos Tube S ga1 and SiC-Mos Tube S ga2 The drive signal is low level. SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 Conduction (i.e.)SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When the drive signal is high, a Phase bridge arm Y a The current is supplied by the inductor L ga1 Flow direction SiC-Mos Tube S ga3 , SiC-Mos Tube S ga4 At this time, the current is from X ga The point flows to the negative terminal of the DC bus, indicating that... X ga The potential at the point is higher than that at the negative terminal of the DC bus. This is due to the diode. D ga1 cathode connection point X ga2 Through inductance L ga2 and X ga Point connection, and diode D ga1 If the anode of the diode is connected to the negative terminal of the DC bus, then the diode... D ga1 The anode voltage is lower than that of the diode. D ga1 The cathode voltage, thereby causing the diode D ga1 The diode will not conduct under reverse voltage, and no current will flow through it. D ga1 Due to diodes D ga2 The cathode is connected to the positive terminal of the DC bus, and the diode... D ga2 anode connection point X ga1 pass SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When connected to the negative terminal of the DC bus, the diode... D ga2 The anode voltage is lower than that of the diode. D ga2 The cathode voltage, thereby causing the diode D ga2 The diode will not conduct under reverse voltage, and no current will flow through it. D ga2 .

[0115] In the shutdown energy feedback circuit, the switching transistors of each phase bridge arm are turned on or off by drive signals generated by the energy feedback control module.

[0116] Specifically, in some embodiments, the combined switching devices used in the motor drive circuit and the shutdown energy feedback circuit are... SiC - Mos The tube is 600V SiC - Mos Tube.

[0117] In some embodiments, see continue to see Figure 1 The motor control module 500 includes:

[0118] dq The shaft reference voltage setpoint module 501 obtains the value based on the system running time and switching time. d The actual rise slope of the shaft reference voltage Regarding the above d The actual rise slope of the shaft reference voltage After integration and amplitude limiting, the result is obtained d Shaft reference voltage setpoint , and given q Shaft reference voltage setpoint The value of is always 0;

[0119] Angle setting module 502, ramping up the reference setpoint for rotational speed. n ramp The actual reference speed setpoint is obtained by limiting the amplitude. n ref Based on the actual reference speed set value n ref Calculate the reference setpoint for the electrical angle. ω eref For electrical angle reference setpoint ω eref Integrating the results yields the operating electrical angle of the air conditioner compressor. θ m Regarding the electrical angle θ m Perform trigonometric operations to obtain the sine value of the angle corresponding to the rotating coordinate system of the air conditioner compressor. θ m And cosine value cos θ m ;

[0120] Two-phase voltage modulation wave conversion module I503, will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ;

[0121] The three-phase voltage modulation wave conversion module I504 converts the two-phase static coordinate system... α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system;

[0122] The sinusoidal modulation module I505 normalizes the three-phase voltage modulation wave to obtain a normalized three-phase voltage modulation wave. Based on the normalized three-phase voltage modulation wave and the triangular carrier wave... Z m The magnitude comparison generates the drive signal for the combined switching device in the motor drive circuit.

[0123] dq The shaft reference voltage setpoint module 501 determines the voltage based on the system running time and switching time. d The actual slope of the shaft reference voltage is obtained by integrating and then limiting it. d The shaft reference voltage is set to a specific value. This method effectively controls the motor's starting process, ensuring a smooth current rise during startup and preventing shocks to the motor and power grid caused by sudden current changes. Simultaneously, it will... q The shaft reference voltage setpoint is kept constant at 0, which helps simplify the control logic and ensures that the motor mainly operates under load during the initial startup phase. d The shaft voltage is controlled to achieve more precise start-up control.

[0124] It should be noted that the system running time refers to the time from when the drive system's power is turned on and the output drive signal PWM begins to be output, until control stops and the drive signal PWM is no longer output. The switching time refers to the time after the drive system starts outputting the drive signal PWM, waiting for the energy feedback control module 600 to control the DC bus voltage to reach a suitable value (e.g., 530V). After the switching time, the given motor control module 500... dq Shaft reference voltage to prevent a sudden drop in bus voltage caused by synchronous motor starting by the motor control module 500.

[0125] The angle setting module 502 limits the ramp-up value of the speed reference setpoint to obtain the actual reference speed setpoint, and calculates the electrical angle reference setpoint accordingly, thereby obtaining the operating electrical angle of the air conditioning compressor. This processing method can ensure a smooth increase in motor speed, avoid mechanical stress and current fluctuations caused by excessively rapid speed changes, and thus improve the stability and reliability of motor operation.

[0126] Two-phase voltage modulation wave conversion module I503 will d shaft and q The shaft reference voltage setpoint is transformed into a two-phase stationary coordinate system. α shaft and β The shaft voltage modulation wave and three-phase voltage modulation wave transformation module I504 further transform the voltage modulation wave in the two-phase stationary coordinate system into a three-phase voltage modulation wave in the three-phase stationary coordinate system. This transformation process enables precise control of the motor voltage, resulting in a more reasonable voltage distribution and improved motor operating efficiency and power factor.

[0127] The sinusoidal modulation module I505 normalizes the three-phase voltage modulation wave and generates the drive signal for the combined switching devices in the motor drive circuit by comparing the magnitude of the normalized three-phase voltage modulation wave with that of the triangular carrier wave. This modulation method can further optimize the voltage control of the motor, actively perform power factor correction, reduce harmonic content, effectively reduce the input current distortion rate, make the motor current waveform closer to a sine wave, reduce electromagnetic interference and noise of the motor, and improve the operating quality of the motor.

[0128] In some embodiments, see Figure 11 , dq The shaft reference voltage setting module is based on the system running time. Time With switching time T on The size is obtained d The actual rise slope of the shaft reference voltage The method is as follows:

[0129] Compare system runtime Time With switching time T on Size;

[0130] If system uptime Time Greater than the switching time T on ,but d The actual slope of the shaft reference voltage is... d The rising slope of the reference voltage on the axis V slope If the system uptime Time Less than switching time Ton ,but d The actual slope of the shaft reference voltage is 0.

[0131] In some embodiments, see Figure 12 The angle setting module sets the value based on the actual reference rotational speed. n ref Calculate the reference setpoint for the electrical angle. ω eref The method is as follows:

[0132] Set the actual reference speed value n ref Multiply by 2 × π / 60 to obtain the reference value of the mechanical angular velocity. ω mref ;

[0133] Mechanical angular velocity reference setpoint ω mref Multiply by permanent magnet series poles Divide by 2 to get the electrical angle reference value. ω eref .

[0134] In some embodiments, see Figure 13 The two-phase voltage modulation wave conversion module I will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows:

[0135] d Shaft reference voltage setpoint cos θ m Obtain intermediate variables v mαp1 , q Shaft reference voltage setpoint Multiply by sin θ m Obtain intermediate variables v mαp2 intermediate variables v mαp1 Subtract intermediate variables v mαp2 get α Axis voltage modulated wave ;

[0136] d Shaft reference voltage setpoint Multiply by sinθ m Obtain intermediate variables v mβp1 , q Shaft reference voltage setpoint cos θ m Obtain intermediate variables v mβp2 intermediate variables v mβp1 Add intermediate variables v mβp2 get β Axis voltage modulated wave .

[0137] In some embodiments, see Figure 14 The three-phase voltage modulation wave conversion module I will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows:

[0138] a Phase voltage modulation wave equal α Axis voltage modulated wave ;

[0139] α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. v tempα1 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ1 ;

[0140] intermediate variables v tempβ1 Subtract intermediate variables v tempα1 ,get b Phase voltage modulation wave ;

[0141] intermediate variables v tempα1 Subtract the intermediate variable after taking the negative value v tempβ1 ,get c Phase voltage modulation wave .

[0142] In some embodiments, see Figure 15The method by which the sinusoidal modulation module I normalizes the three-phase voltage modulation wave to obtain the normalized three-phase voltage modulation wave is as follows: ... a Phase voltage modulation wave 、b Phase voltage modulation wave , c Phase voltage modulation wave Divide by V dc / 2 is normalized a Phase voltage modulation wave Standardized b Phase voltage modulation wave Standardized c Phase voltage modulation wave .

[0143] In some embodiments, the sinusoidal modulation module I modulates the three-phase voltage modulation wave after standardization with a triangular carrier wave. Z m The method for generating the drive signal for the combined switching device in the motor drive circuit by comparing the magnitudes is as follows:

[0144] The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z m Size;

[0145] like Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S mi1 PWM drive signal mi1 and SiC-Mos Tube S mi2 PWM drive signal mi2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S mi3 PWM drive signal mi3 and SiC-Mos Tube S mi4 PWM drive signal mi4 Low level;

[0146] like Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained.SiC-Mos Tube S mi1 PWM drive signal mi1 and SiC-Mos Tube S mi2 PWM drive signal mi2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S mi3 PWM drive signal mi3 and SiC-Mos Tube S mi4 PWM drive signal mi4 It is a high level.

[0147] Specifically, in some embodiments, triangular carriers Z m It is a triangular carrier with a maximum value of 1, a minimum value of -1, and a width of 50μs.

[0148] Specifically, in some embodiments, see further details. Figure 15 Generate the motor drive circuit a The method for driving signals for phase bridge arm combination switching devices is as follows:

[0149] The normalized parts are compared using a comparator. a Phase voltage modulation wave With triangular carrier Z m Size;

[0150] like a Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S ma1 PWM drive signal ma1 and SiC-Mos Tube S ma2 PWM drive signal ma2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S ma3 PWM drive signal ma3 and SiC-Mos Tube S ma4 PWM drive signal ma4 Low level;

[0151] like a Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S ma1 PWM drive signal ma1 and SiC-Mos Tube S ma2 PWM drive signal ma2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S ma3 PWM drive signal ma3 and SiC-Mos Tube S ma4 PWM drive signal ma4 It is a high level.

[0152] In some embodiments, see continue to see Figure 15 Generate the motor drive circuit b The method for driving signals for phase bridge arm combination switching devices is as follows:

[0153] The normalized parts are compared using a comparator. b Phase voltage modulation wave With triangular carrier Z m Size;

[0154] like b Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S mb1 PWM drive signal mb1 and SiC-Mos Tube S mb2 PWM drive signal mb2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S mb3 PWM drive signal mb3 and SiC-Mos Tube S mb4 PWM drive signal mb4 Low level;

[0155] like b Phase voltage modulation wave Less than triangular carrier Z mWhen the comparator outputs a low level, the result is obtained. SiC-Mos Tube S mb1 PWM drive signal mb1 and SiC-Mos Tube S mb2 PWM drive signal mb2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S mb3 PWM drive signal mb3 and SiC-Mos Tube S mb4 PWM drive signal mb4 It is a high level.

[0156] In some embodiments, see continue to see Figure 15 Generate the motor drive circuit c The method for driving signals for phase bridge arm combination switching devices is as follows:

[0157] The normalized parts are compared using a comparator. c Phase voltage modulation wave With triangular carrier Z m Size;

[0158] like c Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S mc1 PWM drive signal mc1 and SiC-Mos Tube S mc2 PWM drive signal mc2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S mc3 PWM drive signal mc3 and SiC-Mos Tube S mc4 PWM drive signal mc4 Low level;

[0159] like c Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. SiC-Mos Tube Smc1 PWM drive signal mc1 and SiC-Mos Tube S mc2 PWM drive signal mc2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S mc3 PWM drive signal mc3 and SiC-Mos Tube S mc4 PWM drive signal mc4 It is a high level.

[0160] In some embodiments, see continue to see Figure 1 The energy feedback control module 600 includes:

[0161] The two-phase voltage modulation waveform conversion module II601 converts the shutdown energy feedback circuit in a rotating coordinate system. d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ;

[0162] The three-phase voltage modulation wave conversion module II602 converts the two-phase static coordinate system into a single phase voltage modulation wave. α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system;

[0163] The sinusoidal modulation module II 603 normalizes the three-phase voltage modulation wave to obtain a normalized three-phase voltage modulation wave. Based on the normalized three-phase voltage modulation wave and the triangular carrier wave... Z g The magnitude comparison generates the drive signal for the combined switching device in the shutdown energy feedback circuit.

[0164] In some embodiments, see Figure 16 The two-phase voltage modulation wave conversion module II will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows:

[0165] d Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gαp1 , q Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gαp2 intermediate variables v gαp1 Subtract intermediate variables v gαp2 get α Axis voltage modulated wave ,in, θ g The angle corresponding to the rotating coordinate system of the shutdown energy feedback circuit;

[0166] d Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gβp1 , q Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gβp2 intermediate variables v gβp1 Add intermediate variables v gβp2 get β Axis voltage modulated wave .

[0167] In some embodiments, see Figure 17 The three-phase voltage modulation wave conversion module II will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows:

[0168] a Phase voltage modulation wave equal α Axis voltage modulated wave ;

[0169] α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable.v tempα2 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ2 ;

[0170] intermediate variables v tempβ2 Subtract intermediate variables v tempα2 ,get b Phase voltage modulation wave ;

[0171] intermediate variables v tempα2 Subtract the intermediate variable after taking the negative value v tempβ2 ,get c Phase voltage modulation wave .

[0172] Specifically, see Figure 18 The method by which the sinusoidal modulation module II normalizes the three-phase voltage modulation wave to obtain the normalized three-phase voltage modulation wave is as follows: ... a Phase voltage modulation wave 、b Phase voltage modulation wave , c Phase voltage modulation wave Divide by V dc / 2 is normalized a Phase voltage modulation wave Standardized b Phase voltage modulation wave Standardized c Phase voltage modulation wave .

[0173] In some embodiments, the sinusoidal modulation module II modulates the three-phase voltage modulation wave after standardization with a triangular carrier wave. Z g The method for generating the drive signal for the combined switching device in the shutdown energy feedback circuit by comparing the magnitudes is as follows:

[0174] The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z g Size;

[0175] like Phase voltage modulation wave Greater than or equal to triangular carrier Z gWhen the comparator outputs a high level, the result is obtained. SiC-Mos Tube S gi1 PWM drive signal gi1 and SiC-Mos Tube S gi2 PWM drive signal gi2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S gi3 PWM drive signal gi3 and SiC-Mos Tube S gi4 PWM drive signal gi4 Low level;

[0176] like Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S gi1 PWM drive signal gi1 and SiC-Mos Tube S gi2 PWM drive signal gi2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S gi3 PWM drive signal gi3 and SiC-Mos Tube S gi4 PWM drive signal gi4 It is a high level.

[0177] Specifically, in some embodiments, triangular carriers Z g It is a triangular carrier with a maximum value of 1, a minimum value of -1, and a width of 50μs.

[0178] Specifically, in some embodiments, see further details. Figure 18 In the shutdown energy feedback circuit, a The method for driving signals for phase bridge arm combination switching devices is as follows:

[0179] The normalized parts are compared using a comparator. a Phase voltage modulation wave With triangular carrier Z g Size;

[0180] like aPhase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S ga1 PWM drive signal ga1 and SiC-Mos Tube S ga2 PWM drive signal ga2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S ga3 PWM drive signal ga3 and SiC-Mos Tube S ga4 PWM drive signal ga4 Low level;

[0181] like a Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S ga1 PWM drive signal ga1 and SiC-Mos Tube S ga2 PWM drive signal ga2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S ga3 PWM drive signal ga3 and SiC-Mos Tube S ga4 PWM drive signal ga4 It is a high level.

[0182] Specifically, in some embodiments, see further details. Figure 18 In the shutdown energy feedback circuit, b The method for driving signals for phase bridge arm combination switching devices is as follows:

[0183] The normalized parts are compared using a comparator. b Phase voltage modulation wave With triangular carrier Z g Size;

[0184] like b Phase voltage modulation wave Greater than or equal to triangular carrier Zg When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S gb1 PWM drive signal gb1 and SiC-Mos Tube S gb2 PWM drive signal gb2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S gb3 PWM drive signal gb3 and SiC-Mos Tube S gb4 PWM drive signal gb4 Low level;

[0185] like b Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S gb1 PWM drive signal gb1 and SiC-Mos Tube S gb2 PWM drive signal gb2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S gb3 PWM drive signal gb3 and SiC-Mos Tube S gb4 PWM drive signal gb4 It is a high level.

[0186] Specifically, in some embodiments, see further details. Figure 18 In the shutdown energy feedback circuit, c The method for driving signals for phase bridge arm combination switching devices is as follows:

[0187] The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z g Size;

[0188] like c Phase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. SiC-Mos TubeS gc1 PWM drive signal gc1 and SiC-Mos Tube S gc2 PWM drive signal gc2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S gc3 PWM drive signal gc3 and SiC-Mos Tube S gc4 PWM drive signal gc4 Low level;

[0189] like c Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S gc1 PWM drive signal gc1 and SiC-Mos Tube S gc2 PWM drive signal gc2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S gc3 PWM drive signal gc3 and SiC-Mos Tube S gc4 PWM drive signal gc4 It is a high level.

[0190] To verify the effectiveness of the energy feedback high power factor air conditioner compressor drive system described in this invention, a simulation model was built using Simulink for verification.

[0191] A simulation model of an energy-feedback high power factor air conditioner compressor drive system was built in Simulink. The effective value of the three-phase power grid line voltage is 380V, and the three-phase filter inductors are... L a , L b , L c All are 2mH DC bus electrolytic capacitors C dc The parameters of the 1000μF permanent magnet synchronous motor M are as follows: stator resistance 0.63Ω, direct-axis inductance 0.00268H, quadrature-axis inductance 0.00347H, flux linkage 0.42Wb, and moment of inertia 0.0057kg / m.2 The number of pole pairs is 3, and the motor speed is set to 1000 r / min. The energy feedback control module... d Shaft reference voltage setpoint Set to 310V. q Shaft reference voltage setpoint Set to 2V, the corresponding angle of the rotating coordinate system of the shutdown energy feedback circuit. θ g The frequency is set to 314.16 rad / s, and the initial phase is -1.5708 rad; in the motor control module, dq Shaft reference voltage given module d The rising slope of the reference voltage on the axis V slope Set to 1552.9V / s, switching time T on Set to 0.002s, the integrator's limit is 132V; the ramp-up value of the speed reference setpoint in the angle setpoint module. n ramp The limiter is set to 11765 r / (min·s), with an upper limit of 1000 r / min and a lower limit of 0 r / min. Figure 19 For traditional air conditioning compressor drive systems a The phase grid voltage and current, and the grid current input to the entire system are sawtooth-shaped pulses with a high distortion rate, resulting in a very low power factor; from Figure 20 It can also be seen that the DC bus voltage of the traditional air conditioning compressor drive system fluctuates greatly, which is not conducive to stable and high-performance air conditioning compressor control. Figure 21 The grid voltage and current waveforms of the high power factor air conditioning compressor drive system with energy feedback function proposed in this invention are shown. The grid voltage and current are in phase, the power factor is very high, close to 1, and the grid current has a high sinusoidal degree. Figure 22 It can be seen that the DC bus voltage of the energy-feedback high power factor air conditioning compressor system proposed in this invention is relatively stable, which is beneficial to the stable and high-performance control of the air conditioning compressor. The above results demonstrate the effectiveness of the energy-feedback high power factor air conditioning compressor drive system described in this invention.

[0192] The above embodiments are used to explain the present invention, but not to limit the present invention. Any modifications and changes made to the present invention within the spirit and scope of the claims shall fall within the protection scope of the present invention.

Claims

1. An energy feedback high power factor air conditioner compressor drive system, characterized by, Comprise: A DC bus; A motor drive circuit, the motor drive circuit is a three-phase completely symmetrical bridge circuit composed of combination switching devices as bridge arms, the second connection end I of each phase bridge arm is connected to the positive pole of the DC bus, and the second connection end II of each phase bridge arm is connected to the negative pole of the DC bus; a permanent magnet synchronous motor, the permanent magnet synchronous motor having a first connection end of the phase bridge arm is connected to the motor drive circuit a first connection end of the phase bridge arm is connected to the motor drive circuit A motor control module for generating a drive signal of the combination switching device in the motor drive circuit; a shutdown energy feedback circuit, the shutdown energy feedback circuit being a three-phase fully symmetrical bridge circuit consisting of the combined switching devices as bridge arms, the first connection of the phase bridge arm is connected to the phase filter inductance is connected to the phase grid voltage, the second connection I of each phase bridge arm is connected to the positive pole of the DC bus, and the second connection II of each phase bridge arm is connected to the negative pole of the DC bus. An energy feedback control module for generating a drive signal of the combination switching device in the shutdown energy feedback circuit; Direct current bus electrolytic capacitor C dc , connected between the shutdown energy feedback circuit and the motor drive circuit, the direct current bus electrolytic capacitor C dc has two ends respectively connected to the positive and negative poles of the direct current bus.

2. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 1, wherein, The combination switching device comprises: A first connection end; A second connection end comprising a second connection end I and a second connection end II; An inductance component comprising inductance I and inductance II, the first end of inductance I and the first end of inductance II are connected to the first connection end; Switching circuit I, including diode I and... SiC-Mos Pipe I and SiC-Mos The first series circuit formed by connecting tubes II in series; SiC-Mos Source connection of tube I SiC-Mos The drain of tube II, SiC-Mos The drain of tube I is connected to the second connection terminal I; SiC-Mos The source of diode II is connected to the cathode of diode I. SiC-Mos The connection point between the source of diode II and the cathode of diode I is connected to the second terminal of inductor II, and the anode of diode I is connected to the second connection terminal II; The switch circuit II comprises a diode II and a second series circuit formed by a transistor III and a transistor IV connected in series; SiC-Mos SiC-Mos The source of the transistor III is connected to the drain of the transistor IV, SiC-Mos The drain of the transistor IV is connected to the second connection terminal II, SiC-Mos The drain of the transistor III is connected to the anode of the diode II, SiC-Mos The connection point of the drain of the transistor III and the anode of the diode II is connected to the second end of the inductor I, SiC-Mos The cathode of the diode II is connected to the second connection terminal I, SiC-Mos The source of the transistor IV is connected to the second connection terminal II.​ 3. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 1, wherein, The motor control module comprises: Dq axis reference voltage given module, according to the system running time and the size of the switching time d axis reference voltage actual rising slope , the d axis reference voltage actual rising slope after integration, the amplitude is limited to obtain d axis reference voltage given value , and give q axis reference voltage given value The value of 0 is constant; angle specifying module, ramping up the reference value of the rotational speed to a specified value n ramp clipping to obtain an actual reference value of the rotational speed n ref , calculating an electrical angle reference value according to the actual reference value of the rotational speed n ref , integrating the electrical angle reference value to obtain an electrical angle of the operation of the air conditioner compressor ω eref , performing a trigonometric operation on the electrical angle to obtain a sine value sin of the corresponding angle in the rotating coordinate system of the air conditioner compressor ω eref , and a cosine value cos θ m θ m θ m θ m ;​​​ The two-phase voltage modulation wave conversion module I, will d The axis reference voltage given value And q The axis reference voltage given value Convert into the two-phase stationary coordinate system α The axis voltage modulation wave And β The axis voltage modulation wave ; The three-phase voltage modulation wave conversion module I converts the two-phase static coordinate system-based α axis voltage modulation wave and β axis voltage modulation wave into the three-phase static coordinate system-based three-phase voltage modulation wave; The sinusoidal modulation module I performs normalization processing on the three-phase voltage modulation wave to obtain a normalized three-phase voltage modulation wave, and generates a drive signal of a combination switch device in the motor drive circuit according to a size comparison between the normalized three-phase voltage modulation wave and a triangular carrier wave Z m ​ 4. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 3, wherein, The two-phase voltage modulation wave conversion module I converts d axis reference voltage given value and q axis reference voltage given value into α axis voltage modulation wave and β axis voltage modulation wave The method is: d axis reference voltage given value multiply cos θ m get intermediate variable v mαp1 , q axis reference voltage given value multiply sin θ m get intermediate variable v mαp2 , intermediate variable v mαp1 subtract intermediate variable v mαp2 get α axis voltage modulation wave ; d axis reference voltage given value multiply sin θ m get intermediate variable v mβp1 , q axis reference voltage given value multiply cos θ m get intermediate variable v mβp2 , intermediate variable v mβp1 add intermediate variable v mβp2 get β axis voltage modulation wave .

5. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 3, wherein, The three-phase voltage modulation wave conversion module I converts α axis voltage modulation wave and β axis voltage modulation wave The method for converting the axis voltage modulation wave into the three-phase voltage modulation wave is: a phase voltage modulation wave equal to α axis voltage modulation wave ; α axis voltage modulation wave multiply 1 / 2, get intermediate variable v tempα1 ; β axis voltage modulation wave multiply 0.866, get intermediate variable v tempβ1 ; Intermediate variable v tempβ1 Subtracting intermediate variable v tempα1 , resulting in b Phase voltage modulation wave ; intermediate variable v tempα1 subtracts the intermediate variable after taking the negative value v tempβ1 , resulting in c phase voltage modulation wave .

6. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 3, wherein, The sinusoidal modulation module I modulates the three-phase voltage after standardization with a triangular carrier wave Z m The method for generating the drive signal of the combined switching device in the motor drive circuit by comparing the size of the three-phase voltage after standardization with the triangular carrier wave is: The normalized values are compared by a comparator Phase voltage modulation wave With the triangular carrier Z m Magnitude; If phase voltage modulation wave greater than or equal to triangular carrier Z m , the comparator output is high, and SiC-Mos tube I S mi1 the driving signal PWM mi1 of SiC-Mos tube II S mi2 the driving signal PWM mi2 of SiC-Mos tube III S mi3 the driving signal PWM mi3 of SiC-Mos tube IV S mi4 the driving signal PWM mi4 is low; If phase voltage modulation wave less than the triangular carrier wave Z m , the comparator output low level, get SiC-Mos tube I S mi1 drive signal PWM mi1 and SiC-Mos tube II S mi2 drive signal PWM mi2 low, low level after the NOT get SiC-Mos tube III S mi3 drive signal PWM mi3 and SiC-Mos tube IV S mi4 drive signal PWM mi4 high.

7. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 1, wherein, The energy feedback control module comprises: Two-phase voltage modulation wave conversion module II, the shutdown energy feedback circuit in the rotating coordinate system is converted into the two-phase static coordinate system d axis reference voltage given value and q axis reference voltage given value converted into the two-phase static coordinate system α axis voltage modulation wave and β axis voltage modulation wave ; The three-phase voltage modulation wave conversion module II converts the two-phase static coordinate system-based α axis voltage modulation wave and β axis voltage modulation wave into a three-phase static coordinate system-based three-phase voltage modulation wave; The sinusoidal modulation module II performs normalization processing on the three-phase voltage modulation wave to obtain a normalized three-phase voltage modulation wave, and generates a drive signal of a combination switch device in the shutdown energy feedback circuit according to a size comparison between the normalized three-phase voltage modulation wave and a triangular carrier wave Z g ​ 8. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 7, wherein, The two-phase voltage modulation wave conversion module II converts d the axis reference voltage given value and q the axis reference voltage given value into α the axis voltage modulation wave and β the axis voltage modulation wave The method is as follows: d axis reference voltage given value multiply cos θ g get intermediate variable v gαp1 , q axis reference voltage given value multiply sin θ g get intermediate variable v gαp2 , intermediate variable v gαp1 subtract intermediate variable v gαp2 get α axis voltage modulation wave wherein, θ g is the angle corresponding to the rotating coordinate system of the shutdown energy feedback circuit; d axis reference voltage given value multiply sin θ g get intermediate variable v gβp1 , q axis reference voltage given value multiply cos θ g get intermediate variable v gβp2 , intermediate variable v gβp1 add intermediate variable v gβp2 get β axis voltage modulation wave .

9. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 7, wherein, The three-phase voltage modulation wave conversion module II converts α axis voltage modulation wave and β axis voltage modulation wave The method for converting the axis voltage modulation wave into the three-phase voltage modulation wave is: a phase voltage modulation wave equal to α axis voltage modulation wave ; α axis voltage modulation wave multiply by 1 / 2, get intermediate variable v tempα2 ; β axis voltage modulation wave multiply by 0.866, get intermediate variable v tempβ2 ; Intermediate variable v tempβ2 Subtracting intermediate variable v tempα2 , resulting in b Phase voltage modulation wave ; intermediate variable v tempα2 subtracts the intermediate variable after taking the negative value v tempβ2 , resulting in c phase voltage modulation wave .

10. The energy feedback high power factor air conditioner compressor drive system as set forth in claim 7, wherein, The sinusoidal modulation module II modulates the three-phase voltage after standardization with a triangular carrier wave Z g The method for generating the drive signal of the combined switching device in the shutdown energy feedback circuit is: The normalized values are compared by a comparator Phase voltage modulation wave With the triangular carrier Z g The size of the triangular carrier If phase voltage modulation wave greater than or equal to triangular carrier Z g , the comparator output high level, get SiC-Mos tube I S gi1 drive signal PWM gi1 and SiC-Mos tube II S gi2 drive signal PWM gi2 high level, high level after taking NOT after getting SiC-Mos tube III S gi3 drive signal PWM gi3 and SiC-Mos tube IV S gi4 drive signal PWM gi4 low level; If phase voltage modulation wave less than triangular carrier Z g the comparator output low level, get SiC-Mos tube I S gi1 drive signal PWM gi1 and SiC-Mos tube II S gi2 drive signal PWM gi2 low level, low level after the NOT get SiC-Mos tube III S gi3 drive signal PWM gi3 and SiC-Mos tube IV S gi4 drive signal PWM gi4 high level.

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