Magnetoelectric dipole antenna with polarization and reconfigurable directional diagram

Abstract

The invention relates to the technical field of antennas, and discloses a magnetoelectric dipole antenna with polarization and reconfigurable directional diagram, which comprises a reflection cavity arranged in a nested manner, a vertical metal wall, a dielectric substrate arranged on the metal wall, and a radiation unit, a stepped parasitic unit, a crossed dipole type feed structure and two groups of switches which are arranged on the lower surface of the substrate. The first group of switches is integrated in the feed structure, and the second group of switches is arranged between the radiation unit and the parasitic unit. Different dipole arms of the feed structure are selectively excited through the first group of switches, and different parasitic units are conducted in combination with the second group of switches, so that the antenna realizes three modes of left-handed and right-handed circular polarization, beam deflection linear polarization and axial radiation linear polarization. Through cooperative work of two groups of switches, multiple working modes are integrated in a single structure, good impedance matching and stable far-field radiation performance are maintained in all modes, the number of used antennas is reduced, and the problem of electromagnetic compatibility caused by introduction of multiple antennas is avoided.

Description

Technical Field

[0001] This invention relates to the field of antenna technology, specifically to a magnetoelectric dipole antenna that combines polarization and pattern reconfigurability. Background Technology

[0002] Magnetoelectric dipole antennas have been widely used in modern wireless communication systems due to their advantages such as wide impedance bandwidth, stable gain and radiation pattern, low backlobe radiation, and low profile. With the continuous development of communication technology, antenna systems are required to have stronger environmental adaptability and greater functional integration. Reconfigurable antennas have emerged to meet this need. They can switch between different operating modes by changing their physical structure or current distribution to meet the communication requirements of different scenarios.

[0003] Combining reconfigurable technology with magnetoelectric dipole antennas is an important direction for improving antenna functionality. Currently, achieving antenna functional reconfiguration typically relies on integrating active devices such as PIN diodes, varactor diodes, or microelectromechanical system (MEMS) switches into the antenna structure. However, integrating these active devices and their bias networks into the antenna's radiating structure or feed network introduces significant design challenges. The introduction of active devices and their bias circuitry inevitably alters the antenna's original surface current distribution, often leading to a deterioration in the antenna's impedance matching characteristics and radiation efficiency within its operating bandwidth.

[0004] Furthermore, achieving multi-dimensional, multi-state reconfiguration, including polarization agility and beam pattern control, presents even greater technical challenges. Switching control structures used to achieve one reconfiguration function (such as beam deflection) often introduce unfavorable coupling and interference to the electromagnetic characteristics required for another reconfiguration function (such as circular polarization). For example, the asymmetric phase distribution introduced to achieve beam deflection can disrupt the field orthogonality condition necessary for achieving high-purity circular polarization, and vice versa. To balance performance under different operating modes, existing solutions often employ complex multilayer dielectric substrate structures or complex feed networks. However, this not only increases the antenna's profile height, manufacturing cost, and process complexity but also sacrifices the inherent broadband advantage of magnetoelectric dipole antennas due to the introduction of more resonant structures.

[0005] Therefore, how to integrate both polarization and pattern reconfiguration functions into a compact magnetoelectric dipole antenna structure, and ensure that the antenna maintains good broadband, high efficiency and high performance radiation characteristics in all operating states, is a technical problem to be solved in the current antenna technology field. Summary of the Invention

[0006] To address the shortcomings of existing technologies, this invention provides a magnetoelectric dipole antenna that combines polarization and pattern reconfigurability, solving the problems of limited antenna reconfiguration function and difficulty in balancing structure and performance in existing technologies.

[0007] To achieve the above objectives, the present invention provides the following technical solution: a magnetoelectric dipole antenna with both polarization and pattern reconfigurability, comprising:

[0008] A rectangular dielectric substrate;

[0009] Four radiating units with chamfered corners are disposed on the lower surface of the dielectric substrate, which are used to form an electric dipole;

[0010] Eight vertically placed metal walls, with adjacent metal walls arranged vertically, support the rectangular dielectric substrate;

[0011] Two reflective cavities with rectangular notches are nested together. The notches in the cavities are not at the same position, and the distance between the two cavities is 0.3mm-0.7mm. The reflective cavities and the vertically placed metal wall together form a magnetic dipole.

[0012] Four stepped parasitic units are symmetrically distributed about the X-axis and Y-axis;

[0013] A cross-dipole type feeding structure is used to excite the radiating element;

[0014] A first set of switches, integrated in the cross-dipole type feed structure, is used to select the polarization mode of the antenna;

[0015] A second set of switches, electrically connected to the radiating unit and the stepped parasitic unit, is used to conduct different stepped parasitic units to obtain a suitable phase difference or guiding unit.

[0016] The phase distribution of the radiating element changes according to array antenna theory. For an array consisting of two elements, the array factor in its far-field pattern function... It can be represented as:

[0017]

[0018] in, The excitation amplitude for a single unit; The wave number is defined as follows: , The wavelength of the antenna in free space; The spacing between two radiating elements; The angle between the far-field direction and the array normal direction; This represents the excitation phase difference between the two radiating elements.

[0019] The second set of switches selectively directs current through the stepped phase delay structure by controlling the current path, thereby introducing a defined excitation phase difference between adjacent radiating elements. According to the above formula, the excitation phase difference The introduction of this will cause the direction of the maximum value of the array factor to be deflected, thereby realizing the pointing reconstruction of the antenna main beam.

[0020] In one embodiment, the two nested reflective cavity structures with rectangular notches include a common metal bottom surface, a first metal wall, and a second metal wall.

[0021] A first rectangular notch is formed on the first metal wall, and a second rectangular notch is formed on the second metal wall at a position complementary to the first rectangular cut-out portion.

[0022] Preferably, the cross-dipole type power supply structure includes four dipole arms and one power supply port; the first set of switching units is disposed between the power supply port and the four dipole arms.

[0023] Furthermore, the four dipole arms include: two dipole arms formed by electrically connecting a triangular metal patch on the upper surface and a rectangular metal patch on the lower surface of the dielectric substrate through metallized vias;

[0024] The two are arrow-shaped dipole arms printed on the lower surface of the dielectric substrate.

[0025] In one specific embodiment, the radiation unit includes four radiation units and four stepped parasitic units; the second set of switches is disposed between the radiation units and the stepped parasitic units.

[0026] Preferably, the stepped parasitic unit is composed of cascaded rectangular metal patches of different widths, used to introduce a preset phase delay for the current flowing through it or as a guiding unit.

[0027] In the left-right circular polarization operating mode, the second set of switches is configured to turn on the two switches at opposite corners, so that current flows through the corresponding two stepped parasitic units.

[0028] In the beam deflection linear polarization operating mode, the second set of switches is configured to turn on two switches on the same side, so that current flows through the corresponding two stepped parasitic units, making them directing units, thereby deflecting the antenna beam.

[0029] In the axial radial polarization operating mode, the second set of switches is configured such that all four switches are turned on, so that current flows through the corresponding four stepped parasitic units.

[0030] Preferably, the inner and outer corners of the radiating metal patch are respectively provided with a first triangular chamfer and a second triangular chamfer to optimize the impedance matching of the antenna.

[0031] In one embodiment, the power supply port includes a first power supply patch connected to the inner conductor of the coaxial cable and a second power supply patch connected to the outer conductor of the coaxial cable;

[0032] The first power supply patch is disposed on the upper surface of the rectangular dielectric substrate, and the second power supply patch is disposed on the lower surface of the dielectric substrate.

[0033] This invention provides a magnetoelectric dipole antenna that combines polarization and pattern reconfigurability. It offers the following advantages:

[0034] 1. This invention achieves a high degree of integration of two reconstruction functions: polarization and radiation pattern. By setting a first set of switches integrated in the cross dipole type feeding structure and a second set of switches located between the radiating element and the stepped parasitic element, a two-level control system is formed. The first set of switches independently selects orthogonal linear polarization excitation, and the second set of switches adjusts the phase distribution or acts as a directional element by changing the current path. Thus, multiple operating modes such as left and right circular polarization, beam deflection linear polarization, and axial radiation linear polarization are achieved on a single antenna structure.

[0035] 2. This invention improves the performance of the antenna in circular polarization mode by employing two nested reflective cavities and complementary first and second rectangular notches on the first and second metal walls, respectively, providing different electromagnetic boundary conditions for left-hand circularly polarized waves and right-hand circularly polarized waves. This optimizes the surface current distribution under the two directions of rotation, thereby broadening the axial ratio bandwidth of the antenna in the two circular polarization modes.

[0036] 3. This invention achieves multiple operating modes such as left and right circular polarization, beam deflection linear polarization, and axial radiation linear polarization by setting eight PIN diodes on a single-layer dielectric substrate, thus avoiding complex multilayer structures or power supply networks. Attached Figure Description

[0037] Figure 1 This is a schematic diagram of the overall antenna structure of the present invention;

[0038] Figure 2 This is a schematic diagram of the antenna structure of the present invention;

[0039] Figure 3 This is a schematic diagram of the cross-dipole type feeding structure of the present invention;

[0040] Figure 4 This is a schematic diagram of the antenna structure of the present invention;

[0041] Figure 5 A schematic diagram of the nested reflective cavity structure of the present invention;

[0042] Figure 6 This is a schematic diagram of the stepped parasitic unit structure of the present invention;

[0043] Figure 7 This is a side view of the antenna of the present invention;

[0044] Figure 8 The figure shows the simulation results of the return loss (S11) of the antenna of the present invention as a function of frequency in the left-hand circular polarization mode.

[0045] Figure 9 The figure shows the simulation results of the axial ratio (AR) of the antenna of the present invention as a function of frequency in the left-hand circular polarization mode;

[0046] Figure 10 The far-field radiation pattern of the antenna of the present invention in the XOZ plane (Phi=0°) at 4.7 GHz in left-hand circular polarization mode is shown.

[0047] Figure 11 The far-field radiation pattern of the antenna of the present invention in the YOZ plane (Phi=90°) at 4.7 GHz in left-hand circular polarization mode;

[0048] Figure 12 The figure shows the simulation results of the return loss (S11) of the antenna of the present invention as a function of frequency in right-hand circular polarization mode.

[0049] Figure 13 The figure shows the simulation results of the axial ratio (AR) of the antenna of the present invention as a function of frequency in the right-hand circular polarization mode.

[0050] Figure 14 The XOZ plane far-field radiation pattern of the antenna of the present invention at 4.7 GHz in right-hand circular polarization mode;

[0051] Figure 15 The antenna of this invention exhibits a far-field radiation pattern in the YOZ plane at 4.7 GHz in right-hand circular polarization mode.

[0052] Figure 16 The figure shows the simulation results of the return loss (S11) of the antenna of the present invention as a function of frequency in the X-ray polarized beam forward deflection mode.

[0053] Figure 17 The radiation pattern of the antenna of the present invention is shown in X-ray polarized beamforward mode at 4.56 GHz.

[0054] Figure 18The figure shows the simulation results of the return loss (S11) of the antenna of the present invention as a function of frequency in the X-ray polarized beam back-off mode.

[0055] Figure 19 The radiation pattern of the antenna of the present invention is shown when it operates in X-ray polarized beam back-off mode at 4.56 GHz.

[0056] Figure 20 The figure shows the simulation results of the return loss (S11) of the antenna of the present invention as a function of frequency in the axial radiation X-ray polarization mode.

[0057] Figure 21 The XOZ plane radiation pattern of the antenna of the present invention when operating in axial radiation X-ray polarization mode at 4.2 GHz;

[0058] Figure 22 The image shows the YOZ plane radiation pattern of the antenna of the present invention operating at 4.2 GHz in axial radiation X-ray polarization mode.

[0059] Figure 23 The figure shows the simulation results of the return loss (S11) of the antenna of the present invention as a function of frequency in the axial radiation Y-polarization mode.

[0060] Figure 24 The XOZ plane radiation pattern of the antenna of the present invention is shown when it operates at 4.2 GHz in the axial radiation Y-polarization mode.

[0061] Figure 25 This is the YOZ plane radiation pattern of the antenna of the present invention when it operates at 4.2 GHz in the axial radiation Y-polarization mode.

[0062] Among them, 1. Crossed dipole type feeding structure; 2. Dielectric substrate; 3. Radiation unit; 4. Metal wall; 5. Semi-rigid coaxial cable; 6. Nested reflective cavity structure; 7. First set of switches; 8. Second set of switches; 101. Triangular metal patch; 102. First feeding patch; 103. Second feeding patch; 104. Metallized via; 105. Rectangular metal patch; 106. Arrow-shaped dipole arm; 107. Coaxial cable inner conductor; 108. Coaxial cable outer conductor; 109. Matching inductor; 301. Radiation metal patch; 302. Stepped parasitic unit; 303. First triangular chamfer; 304. Second triangular chamfer; 3021. First horizontal segment; 3022. 1. Second horizontal segment; 3023. Third horizontal segment; 401. First vertical metal wall; 402. Second vertical metal wall; 601. First metal wall of the reflective cavity; 602. Second metal wall of the reflective cavity; 603. Common metal bottom surface; 6011. First metal sidewall of the reflective cavity; 6012. First rectangular notch; 6021. Second metal sidewall of the reflective cavity; 6022. Second rectangular notch; 701. First PIN diode; 702. Second PIN diode; 703. Third PIN diode; 704. Fourth PIN diode; 801. Fifth PIN diode; 802. Sixth PIN diode; 803. Seventh PIN diode; 804. Eighth PIN diode. Detailed Implementation

[0063] The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some embodiments of the present invention, and not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of the present invention.

[0064] See attached document Figure 1 To be continued Figure 7 The present invention provides a magnetoelectric dipole antenna with both polarization and pattern reconfigurability, which, in terms of physical structure from bottom to top, includes: a nested reflective cavity structure 6, eight vertically placed metal walls 4, a dielectric substrate 2, four radiating elements 3, a cross dipole type feeding structure 1, a first set of switches 7, and a second set of switches 8.

[0065] In this embodiment, the nested reflective cavity structure 6 forms the base of the antenna, and eight vertically placed metal walls 4 are fixed to the common metal bottom surface 603 of the nested reflective cavity structure 6. The dielectric substrate 2 is horizontally arranged and supported by the upper ends of the eight vertically placed metal walls 4.

[0066] A cross-dipole type feed structure 1 is disposed on the upper and lower surfaces of the dielectric substrate 2. Four radiating elements 3 are used to form the electric dipole portion of the antenna and are printed on the lower surface of the dielectric substrate 2. The metal wall 4 and the common metal bottom surface 603 of the nested reflective cavity structure 6 together form the magnetic dipole portion of the antenna. The electric dipole and the magnetic dipole work together to form a magnetoelectric dipole antenna.

[0067] The reconfigurable function of the antenna is achieved collaboratively by the first set of switches 7 and the second set of switches 8. The first set of switches 7 is integrated in the cross-dipole type feed structure 1 and is used to select the operating polarization of the antenna. The second set of switches 8 is electrically connected to the radiating element 3 and the stepped parasitic element 302 to generate a 90° phase shift or a directing effect.

[0068] The nested reflective cavity structure 6 includes a square common metal base 603, and a first metal wall 601 and a second metal wall 602 of the reflective cavity vertically fixed to the common metal base 603. The first metal wall 601 forms the outer square cavity wall, and the second metal wall 602 forms the inner square cavity wall. This double-layer metal wall design is used to improve the circular polarization bandwidth while suppressing the antenna's back radiation and increasing the antenna's gain.

[0069] Specifically, a first rectangular notch 6012 is provided at the center of one of the first metal sidewalls 6011 of the first metal wall 601 of the reflecting cavity along its length direction. By rotating it 90° in sequence, four notches are obtained on the four sides of the cavity. A second rectangular notch 6022 with the same size as the first rectangular notch 6012 is provided on the second metal wall 602 of the reflecting cavity. The first rectangular notch 6012 and the second rectangular notch 6022 are complementary. This complementary asymmetric opening structure provides different electromagnetic boundary conditions for left-handed and right-handed circularly polarized waves, thereby widening the axial ratio bandwidth of the two circular polarization modes.

[0070] In one specific embodiment, the side length of the common metal bottom surface 603 is 116 mm, the height of both the first metal wall 601 and the second metal wall 602 of the reflective cavity is 26 mm, and the length of both the first rectangular notch 6012 and the second rectangular notch 6022 is 40 mm, and the width of both is 26 mm. Preferably, the spacing between the two nested reflective cavities is set to 0.5 mm. This spacing is precisely positioned by setting an insulating spacer between the first metal wall 601 and the second metal wall 602 of the reflective cavity. The spacer is made of the same RogersRT / duroid5870 material as the dielectric substrate 2, and its thickness is strictly controlled to 0.5 mm. This ensures that the spacing between the two cavities is uniform and stable over a long period of time during assembly, avoiding short circuits caused by excessively small spacing between the two metal walls, and preventing excessively large spacing from weakening the magnetic field confinement effect.

[0071] There are eight metal walls 4. The group directly connected to the radiation unit 3 is divided into four groups. Each group contains two mutually perpendicular first vertical metal walls 401 and second vertical metal walls 402.

[0072] In a preferred embodiment, the common metal bottom surface 603, the first metal wall 601, the second metal wall 602, and the eight vertically placed metal walls 4 of the nested reflector cavity structure 6 need to ensure good electrical contact in order to avoid generating parasitic inductance or capacitance that affects antenna performance.

[0073] In this embodiment, the dielectric substrate 2 is made of RogersRT / duroid5870 material, which has a relative permittivity of 2.33, a loss tangent of 0.0012, a thickness of 0.787 mm, and a size of 62 mm x 62 mm.

[0074] The radiating unit 3 is printed on the lower surface of the dielectric substrate 2 and consists of four square radiating metal patches 301 that are centrally symmetrically distributed.

[0075] To optimize impedance matching characteristics within the antenna's operating bandwidth, each radiating metal patch 301 has a first triangular chamfer 303 and a second triangular chamfer 304 at its inner and outer corners, respectively. These triangular chamfers introduce a capacitive loading effect at specific locations on the patch. This capacitive loading effectively compensates for inductive components generated by probe feeding or the structure itself within the operating frequency band, thereby achieving better impedance matching over a wider frequency range. By precisely adjusting the dimensions (i.e., the lengths of the right-angled sides) of the first and second triangular chamfers 303 and 304, the antenna's resonant point and impedance bandwidth can be precisely controlled, which is one of the key technical means to achieve broadband antenna performance.

[0076] Each radiating metal patch 301 is connected to a stepped parasitic unit 302 on its outer side. The parasitic unit is composed of three rectangular metal patches with different widths and lengths cascaded together, specifically including a first horizontal segment 3021, a second horizontal segment 3022 and a third horizontal segment 3023 connected end to end.

[0077] In this embodiment, the electrical length of the stepped parasitic unit 302 is designed to produce a phase delay of approximately 90° at the center operating frequency (e.g., 3.5 GHz). This phase delay value can be precisely controlled by adjusting the specific lengths and widths of the first horizontal segment 3021, the second horizontal segment 3022, and the third horizontal segment 3023.

[0078] In this embodiment, the cross-dipole type feeding structure 1 consists of two sets of spatially orthogonal dipole arms, which are used to excite linearly polarized radiation in the X and Y directions respectively. The energy is coupled through the cross-dipole type feeding structure 1, thereby exciting the four radiating metal patches 301 to perform electromagnetic radiation.

[0079] Specifically, the first set of dipole arms is a three-dimensional structure disposed on the upper and lower surfaces of the dielectric substrate 2, including two isosceles triangular metal patches 101 disposed on the upper surface of the dielectric substrate 2, two rectangular metal patches 105 disposed on the lower surface of the dielectric substrate 2, and a metallized via 104 connecting the triangular metal patches 101 and the rectangular metal patches 105. The second set of dipole arms consists of two arrow-shaped dipole arms 106 directly printed on the lower surface of the dielectric substrate 2.

[0080] In this embodiment, the antenna is fed through a semi-rigid coaxial cable 5. The inner conductor 107 of the semi-rigid coaxial cable 5 passes through the dielectric substrate 2 and is welded to the first feed patch 102 disposed on the upper surface of the dielectric substrate 2. The outer conductor 108 of the coaxial cable is welded to the second feed patch 103 disposed on the lower surface of the dielectric substrate 2.

[0081] Specifically, a through-hole matching the outer diameter of the semi-rigid coaxial cable 5 is formed at the center of the common metal bottom surface 603. The semi-rigid coaxial cable 5 passes through this through-hole, and its outer conductor 108, after exiting the common metal bottom surface 603, is welded to the common metal bottom surface 603 to form a ground connection, ensuring that the entire reflective cavity structure is at zero potential. Subsequently, the coaxial cable continues to extend upwards, passing through a through-hole pre-reserved in the center of the dielectric substrate 2. Its inner conductor 107 and outer conductor 108 are then welded to the first feed patch 102 and the second feed patch 103, respectively. This multi-point grounding and precise feed port processing method is crucial for suppressing common-mode current and ensuring the stability of the feed network.

[0082] To achieve broadband impedance matching of the antenna within its operating frequency band, a matching inductor 109 in the form of a microstrip line is connected to the end of all dipole arms.

[0083] In this embodiment, both the first set of switches 7 and the second set of switches 8 use PIN diodes. The PIN diodes are kept in the on or off state by controlling the external DC bias circuit, so that the antenna can work in different modes.

[0084] Specifically, the first set of switches 7 includes a first PIN diode 701, a second PIN diode 702, a third PIN diode 703, and a fourth PIN diode 704. These PIN diodes are disposed in a cross-dipole type power supply structure 1. The first PIN diode 701 and the second PIN diode 702 are respectively located between the power supply port and two arrow-shaped dipole arms 106 in the Y direction. The third PIN diode 703 and the fourth PIN diode 704 are respectively located between the power supply port and two dipole arms in the X direction formed by a triangular metal patch 101 on the upper surface of the dielectric substrate 2 and a rectangular metal patch 105 on the lower surface of the dielectric substrate 2.

[0085] The second set of switches 8 includes a fifth PIN diode 801, a sixth PIN diode 802, a seventh PIN diode 803, and an eighth PIN diode 804. Each PIN diode is connected to a radiating unit 3 and its corresponding stepped parasitic unit 302. When the PIN diode is turned on, the current flowing to the corresponding radiating unit 3 is guided through the stepped parasitic unit 302 it is connected to, thereby introducing a preset phase delay and forming left and right circular polarization.

[0086] To verify the performance of the technical solution disclosed in this embodiment, a commercial full-wave electromagnetic simulation software based on the finite element method (such as Ansys HFSS) was used to perform precise numerical analysis and optimization on the constructed antenna model. The following is in conjunction with the appendix... Figure 8 To be continued Figure 21 The key performance indicators of the antenna in each reconfigurable operating mode are described in detail.

[0087] See attached document Figure 8 and attached Figure 9 The figures shown are simulation results of the return loss and axial ratio of the antenna in left-hand circular polarization mode.

[0088] From the appendix Figure 8 As can be seen, in the left-hand circular polarization operating mode, the antenna's return loss S11 is below -10dB in the wide frequency band from 3.7GHz to 5.34GHz, which indicates that the antenna's input port and the feeder system have good impedance matching in this frequency band.

[0089] From the appendix Figure 9 As can be seen, in the left-hand circular polarization operating mode, the antenna's 3dB axial ratio bandwidth (i.e., the band with AR≤3dB) covers the frequency band from 4.44GHz to 5.33GHz, indicating that the antenna can perform left-hand circular polarization radiation in this frequency band.

[0090] See attached document Figure 10 and attached Figure 11These figures show the far-field radiation patterns in the XOZ plane (Phi=0°) and YOZ plane (Phi=90°) at a center frequency of 4.7 GHz when the antenna operates in left-hand circular polarization mode. Simulation results show that in both principal planes, the maximum radiation direction of the antenna's main beam is stable along the normal direction (θ=0°), with no beam shift or splitting. Furthermore, within a 3-dB beamwidth, the cross-polarization component is consistently more than 20 dB lower than the main polarization component. This excellent cross-polarization suppression capability fully demonstrates that the antenna possesses extremely high polarization purity in left-hand circular polarization mode.

[0091] See attached document Figure 12 and attached Figure 13 The figures show the simulation results of the return loss and axial ratio of the antenna in right-hand circular polarization mode.

[0092] From the appendix Figure 12 As can be seen, in the right-hand circular polarization operating mode, the antenna's return loss S11 is below -10dB in a wide frequency band from 3.62GHz to 5.39GHz, which indicates that the antenna also has good port impedance matching characteristics in this state.

[0093] From the appendix Figure 13 As can be seen, the antenna's 3dB axial ratio bandwidth covers the frequency band from 4.54GHz to 5.29GHz, with a relative bandwidth of 15.26%, indicating that the antenna can perform circularly polarized radiation within this frequency band.

[0094] See attached document Figure 14 and attached Figure 15 These figures represent the far-field radiation patterns in the XOZ and YOZ planes at a center frequency of 4.7 GHz when the antenna operates in right-hand circular polarization mode. Simulation results show that within both principal planes, the antenna's main beam consistently points towards the normal direction without any offset or split lobes, exhibiting good symmetry in the radiation pattern. Furthermore, within a 3-dB lobe width, the cross-polarization is less than 18 dB lower than the main polarization, demonstrating excellent circular polarization radiation characteristics.

[0095] See attached document Figure 16 and attached Figure 18 The figure shows the simulation results of the return loss of the antenna in the beam deflection linear polarization mode. In both forward deflection (+xoz plane deflection) and backward deflection (-xoz plane deflection) modes, the return loss S11 of the antenna is less than -10dB in the frequency band from 4.12GHz to 5.43GHz, which verifies that the antenna still maintains its broadband characteristics in the beam deflection linear polarization state.

[0096] See attached document Figure 17 and attached Figure 19These are the radiation patterns of the antenna in forward and backward offset modes at 4.56 GHz, respectively. In forward offset mode, the maximum radiation direction of the antenna's main beam points to θ = +48°, with a peak gain of 7.82 dBi. In backward offset mode, the maximum radiation direction of the antenna's main beam points to θ = -48°, with a peak gain of 7.53 dBi. This clearly shows that by controlling the on / off state of specific PIN diodes in the second set of switches 8, corresponding directional elements are introduced, thereby causing the beam to be offset in the corresponding direction.

[0097] See attached document Figure 20 The figure shows the simulation results of the return loss of the antenna operating in axial radiation X-ray polarization mode. (See attached image.) Figure 20 As can be seen, in the axial radiation X-ray polarization mode, the antenna's -10dB impedance bandwidth covers the frequency band from 4.05GHz to 4.35GHz, indicating that the antenna has good port matching in this frequency band.

[0098] See attached document Figure 21 and attached Figure 22 The figures show the far-field radiation patterns in the XOZ and YOZ planes at 4.2 GHz, respectively, when the antenna operates in axial X-ray polarization mode. The results indicate that the antenna radiates along the axial (+Z axis) direction without any shift in the maximum radiation direction or lobe phenomena, and the cross-polarization is 20 dB lower than the main polarization.

[0099] See attached document Figure 23 The figure shows the simulation results of the return loss of the antenna operating in the axial radiation Y-polarization mode. (See attached image.) Figure 23 As can be seen, in the axially radiating Y-polarized mode, the antenna's -10dB impedance bandwidth covers the frequency band from 3.7GHz to 4.76GHz.

[0100] See attached document Figure 24 and attached Figure 25 The figures show the far-field radiation patterns in the XOZ and YOZ planes at 4.2 GHz, respectively, when the antenna operates in axial radiation Y-polarization mode. The results indicate that the antenna radiates along the axial (+Z axis) direction without any shift in the maximum radiation direction or lobe phenomena, and the cross-polarization is 20 dB lower than the main polarization.

[0101] In summary, the simulation results verify the feasibility and superiority of the technical solution in this embodiment, proving that the antenna design successfully reconstructs the left and right circular polarization modes, beam deflection linear polarization mode, and axial radiation linear polarization mode in a compact structure.

Claims

1. A magnetoelectric dipole antenna with both polarization and pattern reconfigurability, characterized in that, include: A rectangular dielectric substrate; Four radiating units with chamfered corners are disposed on the lower surface of the dielectric substrate, which are used to form an electric dipole; Eight vertically placed metal walls are divided into four groups, with adjacent metal walls arranged perpendicularly to each other, and the metal walls support the rectangular dielectric substrate. Two reflective cavities with rectangular notches are nested together. The notches in the cavities are not at the same position, and the distance between the two cavities is 0.3mm-0.7mm. The reflective cavities and the vertically placed metal wall together form a magnetic dipole. Four stepped parasitic units are symmetrically distributed about the X-axis and Y-axis; A cross-dipole type feeding structure is used to excite the radiating element; A first set of switches, integrated in the cross-dipole type feed structure, is used to select the polarization mode of the antenna; A second set of switches, electrically connected to the radiating unit and the stepped parasitic unit, is used to activate different stepped parasitic units.

2. The magnetoelectric dipole antenna with both polarization and pattern reconfigurability according to claim 1, characterized in that, The two nested reflective cavity structures with rectangular notches include: A common metal base, a first metal wall, and a second metal wall; The first metal wall has a first rectangular notch, and the second metal wall has a second rectangular notch at a position complementary to the first rectangular notch.

3. A magnetoelectric dipole antenna with both polarization and pattern reconfigurability according to claim 1, characterized in that, The cross-dipole type feeding structure includes: Four dipole arms and one feed port; The first set of switching units is disposed between the power supply port and the four dipole arms.

4. A magnetoelectric dipole antenna with both polarization and pattern reconfigurability according to claim 3, characterized in that, The four dipole arms include: Two dipole arms are formed by electrically connecting a triangular metal patch on the upper surface and a rectangular metal patch on the lower surface of the dielectric substrate through metallized vias. The two are arrow-shaped dipole arms printed on the lower surface of the dielectric substrate.

5. A magnetoelectric dipole antenna with both polarization and pattern reconfigurability according to claim 1, characterized in that, The radiating unit is disposed on the lower surface of the dielectric substrate, and the radiating unit is a metal patch with triangular chamfers; The second set of switches is disposed between the radiating unit and the stepped parasitic unit.

6. A magnetoelectric dipole antenna with both polarization and pattern reconfigurability according to claim 5, characterized in that, The stepped parasitic unit is composed of cascaded rectangular metal patches of different widths.

7. A magnetoelectric dipole antenna with both polarization and pattern reconfigurability according to claim 5, characterized in that, The first set of switches is located in the cross-dipole type feeding structure and is used to turn on different dipole arms, thereby enabling the antenna to operate in different polarization modes.

8. A magnetoelectric dipole antenna with both polarization and pattern reconfigurability according to claim 5, characterized in that, The second set of switches is located between the radiating unit and the stepped parasitic unit. By controlling the closing and opening of the second set of switches, different stepped parasitic units can be flexibly selected, thereby obtaining a suitable phase difference or guiding unit.

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