Device and method for testing inverter and / or converter

Abstract

The invention relates to a device for testing an inverter and / or a converter, comprising a first simulation means, a second simulation means, an inverter and / or converter connected between the first simulation means and the second simulation means, comprising intermediate circuit capacitors connected in parallel, and a control means, the first simulation mechanism comprises at least one first current-optimized load module and the second simulation mechanism comprises at least one parallel circuit of a second dynamically-optimized load module and a second current-optimized load module, the first current-optimized load module and the second current-optimized load module each comprising at least two stages of inverters, the second dynamically optimized load module comprises an inverter of at least three stages, and the control device is configured to control the second current optimized load module on the basis of a low-pass filtered output voltage of the inverter and / or the converter and to control the second dynamically optimized load module on the basis of a high-pass filtered output voltage of the inverter and / or the converter.

Description

TECHNICAL FIELD

[0001] The invention relates to a device for testing an inverter and / or a converter, having a first simulation mechanism set up to simulate an energy generator, a second simulation mechanism set up to simulate an energy consumer, an inverter and / or a converter connected between the first and second simulation mechanisms, comprising a parallel connection of intermediate circuit capacitors, and a control mechanism. The invention furthermore relates to a method for testing an inverter and / or a converter, having a first simulation mechanism set up to simulate an energy generator, a second simulation mechanism set up to simulate an energy consumer, and an inverter and / or a converter connected between the first and second simulation mechanisms, comprising a parallel connection of intermediate circuit capacitors. BACKGROUND

[0002] Motors in variable-speed drives are usually operated by means of switched-mode power electronics. The purpose of such power electronics is to apply a variable fundamental frequency current to the motor which is as sinusoidal as possible. The resulting torque causes the motor to rotate at the same electrical rotational frequency ω.

[0003] Since modern power electronics operate at a certain switching frequency fs of, for example, 10 kHz by means of pulse width modulation, a high-frequency triangular switching ripple with a period duration of 1 / fs is superimposed on the desired, sinusoidal motor current fundamental wave with electrical rotational frequency ω.

[0004] In order to realistically map the behavior of an actual motor on switched-mode power electronics by means of an electronic load in the power HIL field, i.e. in a hardware-in-the-loop simulator, it is necessary to simulate the motor current fundamental wave (including the resulting current ripple with the switching frequency fs of the power electronics), wherein the motor current fundamental wave is sought up to a maximum of 5 kHz.

[0005] In applications known from the prior art, fast-switching, current-regulated multi-level converters are applied as current sources for this task. Such inverters are also referred to as load modules. The known load modules are optimized in terms of maximum dynamics, i.e. in terms of the simulation of the motor current ripple in the range of 10 to 100 kHz, as it is generated in the pulsed output stage when operating a motor.

[0006] The maximum high-bandwidth requirement in the case of simultaneously high current regulation accuracy, however, requires a costly power electronics hardware structure. The effective switching frequency f sLoadModule of the load modules for target applications of several 1000 A current ratings in the megawatt (MW) range is therefore located at approximately 800 kHz. The switching frequency f sLoadModulerepresents the frequency at which the load module can impose a new voltage level on the output in order to adjust the desired target current.

[0007] Due to the high switching frequency, however, high switching losses occur. The current that can be achieved relative to the volume structure space is small for such power electronics, however, the cooling costs are relatively high. The corresponding hardware structure is usually complex and expensive. Due to the design of the load modules for dynamics and accuracy, each load module is limited to a current of, for example, 75 A. If a known power HIL system is to be equipped with a current of 1000 A in order to simulate the electric machine of a wind power plant, approximately 14 load modules per phase are required in order to be able to provide the total current required for the simulation of the electric machine, in particular the electric motor.

[0008] Similar problems occur in the simulation of electrical power supply networks in the same high power range. Usually, not only the network fundamental wave should be mapped, but also the network harmonics of higher orders n, which are superimposed on the network fundamental wave. The harmonics have a frequency of n times the fundamental wave and an amplitude of 1 / n times the fundamental wave amplitude.

[0009] Furthermore, in the simulation of high-voltage DC vehicle onboard networks of electric vehicles, on the one hand increasingly high currents must be covered, but on the other hand the high dynamics of the counteraction of the simulated switching power electronics must be covered. SUMMARY

[0010] Based on this situation, the task of the present invention is to propose an electrically circuit-technically simplified device for testing inverters and / or converters and a corresponding method, which enables the greatest possible high bandwidth with simultaneously high current regulation accuracy together with the lowest possible amount of power electronic hardware structure compared to the design solutions known from the prior art.

[0011] The task of the present invention is solved by the features of the independent claim. Advantageous design solutions are proposed in the dependent claims.

[0012] The task is therefore solved by a device for testing inverters and / or converters, having a first simulation mechanism set up for simulating an energy generator, a second simulation mechanism set up for simulating an energy consumer, an inverter and / or converter connected between the first simulation mechanism and the second simulation mechanism, which comprises a parallel connection of intermediate circuit capacitors, and a control mechanism, wherein

[0013] The first simulation mechanism comprises at least one first current-optimized load module and the second simulation mechanism comprises at least one parallel circuit of a second dynamic-optimized load module and a second current-optimized load module,

[0014] The first current-optimized load module and the second current-optimized load module each comprise at least two stages of inverters, and the second dynamically-optimized load module comprises at least three stages of inverters, and

[0015] The control mechanism is designed to control the second current-optimized load module on the basis of a low-pass filtered output voltage of the inverter and / or the converter and to control the second dynamically-optimized load module on the basis of a high-pass filtered output voltage of the inverter and / or the converter.

[0016] The proposed solution is based on the idea that, in contrast to the design known from the prior art, in which, for example, in order to simulate the motor of a wind power plant with a current of 1000 A, approximately 14 load modules per phase are required in order to provide the total current required for the simulation of the electric motor, a parallel circuit of a second dynamically-optimized load module and a second current-optimized load module is implemented, wherein the second current-optimized load module is controlled on the basis of a low-pass filtered output voltage of the inverter and / or the converter and the second dynamically-optimized load module is controlled on the basis of a high-pass filtered output voltage of the inverter and / or the converter.

[0017] In other words, it is considered that the mapping of the motor current ripple, as occurs in the pulsed output stage when the motor is running, in particular in the range of 10 to 100 kHz and / or with an effective switching frequency of approximately 800 kHz, is implemented by means of the dynamically-optimized load module, and the mapping of the motor current fundamental, in particular in the range of 0 to 5 kHz, is implemented by means of the current-optimized load module, which has a comparatively much smaller bandwidth, i.e. in particular for a comparatively very high rated current. In the case of grid simulation and battery simulation, this can be done analogously. Overall, the proposed device allows a great increase in the power density of the power HIL system, while at the same time a cost reduction is achieved compared to conventional devices.

[0018] The first current-optimized load module and the second current-optimized load module are preferably designed identically in terms of physics and / or in particular for high currents and / or bandwidth limitations. The first dynamically-optimized load module and the second dynamically-optimized load module are preferably designed identically in terms of physics and / or in particular for a higher dynamics and accuracy relative to the respective current-optimized load module. By applying such current-optimized load modules, which can be produced more cost-effectively relative to the dynamically-optimized load modules, the device can be produced more cost-effectively. The control mechanism is preferably designed as a microprocessor, a memory programmable controller, a computer mechanism or the like.

[0019] According to a preferred refinement, the inverter and / or the converter are three- phase, the second simulation means comprise for each phase a respective parallel circuit of a second dynamically optimized load module and a second current-optimized load module, and the control means are designed to control the second current-optimized load module of the respective phase on the basis of a low-pass filtered output voltage of the respective phase of the inverter and / or the converter and to control the second dynamically optimized load module of the respective phase on the basis of a high-pass filtered output voltage of the respective phase of the inverter and / or the converter.

[0020] According to a further preferred design, the device comprises an inverter, wherein the control means are designed to control the first current-optimized load module on the basis of an input current of the inverter. By means of this design, a generator with an inverter and a power supply network, for example a wind power plant in the megawatt range, can be simulated.

[0021] According to a preferred refinement, the first simulation means comprise at least one, in particular two, parallel circuits of a first current-optimized load module and a first dynamically optimized load module, and the control means are designed to control the first current-optimized load module on the basis of a low-pass filtered input current of the inverter and to control the first dynamically optimized load module on the basis of a high-pass filtered input current of the inverter.

[0022] According to a further preferred design, the device has a converter, wherein the converter is three-phase, the first simulation means comprise for each phase a respective parallel circuit of a first dynamically optimized load module and a first current-optimized load module, and the control means are designed to control the first current-optimized load module of the respective phase on the basis of a low-pass filtered input voltage of the respective phase of the converter and to control the first dynamically optimized load module of the respective phase on the basis of a high-pass filtered input voltage of the respective phase of the converter.

[0023] According to a preferred refinement, the low-pass filtering is realized with a cut-off frequency of < 5 kHz, in particular < 3 kHz, and the high-pass filtering is realized with a cut-off frequency of > 8 kHz, in particular > 10 kHz. Preferably, the cut-off frequency of the low-pass filtering or the low-pass is chosen such that the motor current fundamental remains unaffected. The motor current fundamental is usually located below 5 kHz. Preferably, the cut-off frequency of the high-pass filtering or the high-pass is chosen such that the resulting motor current ripple component remains unaffected. Usually the cut-off frequency is located in the range of 8 to 10 kHz.

[0024] According to a further preferred design, a plurality of series and / or parallel connected first current-optimized load modules and / or second current-optimized load modules are provided. By means of such a plurality, for example 2, 3, 4 or 5 series and / or parallel connected first current-optimized load modules and / or second current-optimized load modules, higher currents can be simulated in a comparatively simple and likewise more cost-advantageous manner.

[0025] According to one preferred development, the control mechanism comprises an FPGA (field programmable gate array). Preferably, the control mechanism is part of the first simulation mechanism and / or the second simulation mechanism. Likewise, the first simulation mechanism and the second simulation mechanism can be designed as a common simulation mechanism. The simulation mechanism can be designed for accommodating a breadboard, whose functions, for example, have signal measurement, simulation of specific sensor signals, battery simulation, simulation of electrical faults such as short circuits or loose contacts, while other breadboards are available as gateways for different bus standards or for connecting FPGAs.

[0026] According to another preferred design, the first dynamically optimized load module and the second dynamically optimized load module each comprise an inverter of at least seven stages. With such an inverter of seven stages, a frequency range or switching frequency of, for example, 800 kHz can be covered and at the same time a current of up to 75 A can be provided.

[0027] According to one preferred development, the first simulation mechanism comprises a battery and / or a generator and / or and / or the second simulation mechanism comprises an electric motor and / or a power supply network. Preferably, the first simulation mechanism is designed as a battery and / or as a generator, and / or the second simulation mechanism is designed as an electric motor and / or a power supply network or as part of and / or connected to a power supply network. With the proposed device, the above-mentioned components, for example a wind power plant in the megawatt range, can thus be simulated in a simple and in particular cost-advantageous manner.

[0028] This task is furthermore solved by the device according to any of the preceding claims for testing inverters and / or converters of wind power plants, power supply networks and / or batteries, in particular of electric vehicles.

[0029] This task is also solved by a method for testing inverters and / or converters, having a first simulation mechanism set up for simulating an energy generator, a second simulation mechanism set up for simulating an energy consumer, and an inverter and / or converter connected between the first simulation mechanism and the second simulation mechanism, comprising a parallel connection of intermediate circuit capacitors, wherein

[0030] The first simulation mechanism comprises at least one first current-optimized load module and the second simulation mechanism comprises at least one parallel circuit of a second dynamically optimized load module and a second current-optimized load module,

[0031] The first current-optimized load module and the second current-optimized load module each comprise an inverter of at least two stages, and the second dynamically optimized load module comprises an inverter of at least three stages, and comprising the following steps:

[0032] The second current-optimized load module is controlled on the basis of a low-pass filtered output voltage of the inverter and / or converter and

[0033] The output voltage of the inverter and / or converter is controlled by a second dynamically optimized load module based on the high-pass filter of the inverter and / or converter.

[0034] Alternative design options and advantages of the method will be apparent to those skilled in the art to be similar to those of the front toe device. Attached Figure Description

[0035] The invention is further illustrated below with reference to the accompanying drawings and preferred embodiments. The drawings show:

[0036] Figure 1 A schematic apparatus for testing an inverter is shown according to a preferred embodiment;

[0037] Figure 2 A schematic apparatus for testing an inverter is shown according to another preferred embodiment;

[0038] Figure 3 A schematic apparatus for testing a converter is shown according to another preferred embodiment;

[0039] Figure 4 Showing according to Figures 1 to 3 A schematic diagram of the dynamically optimized load module of the device; and

[0040] Figure 5 Showing according to Figures 1 to 3 A schematic diagram of the load optimization load module for the device. Detailed Implementation

[0041] Figures 1 to 3 Schematic diagrams of apparatus for testing inverter 1 and / or converter 2 according to preferred embodiments are shown respectively.

[0042] The corresponding device has a first simulation mechanism 3 for simulating an energy generator and a second simulation mechanism 4 for simulating an energy consumer. Figure 1 and 2 The first simulation mechanism 3 represents the battery model, while Figure 1 and 2 The second simulation mechanism 4 represents the motor model. Figure 3 The first simulation mechanism 3 represents the generator model, while Figure 3 The second simulation mechanism 4 represents the power grid model.

[0043] exist Figure 1 and 2 The intermediate inverter 1 is connected between the first simulation mechanism 3 and the second simulation mechanism 4, wherein the intermediate circuit capacitor 5 is connected in parallel to the inverter 1 on the input side. Figure 3In this circuit, converter 2 is connected between the first simulation mechanism 3 and the second simulation mechanism 4, and the intermediate circuit capacitor 5 is also connected in parallel with the output terminal of the rectifier of converter 2 and in parallel with the input terminal of the inverter of converter 2 in the voltage intermediate circuit. Inverter 1 and converter 2 have known bipolar transistors including insulated gate electrodes and IGBTs, as in the prior art, which include diodes connected in parallel, such as those from... Figures 1 to 3 Clearly visible.

[0044] exist Figure 1 The first simulation mechanism 3 of the design shown has two first current-optimized load modules 6, which are connected to the input terminals of the inverter 1 on the output side, that is, connected to the positive input terminal and the negative input terminal of the inverter 1 respectively. Figure 2 In the design scheme shown, the first simulation mechanism 3 also has two first dynamically optimized load modules 7, which are connected in parallel with two first current optimized load modules 6. Figure 3 The design shown has a parallel circuit of a first current-optimized load module 6 and a first dynamic-optimized load module 7 for each phase. Figures 1 to 3 The second simulation mechanism 4 of the design shown has a parallel circuit of a second current-optimized load module 8 and a second dynamic-optimized load module 9 for each phase.

[0045] The first dynamically optimized load module 7 and the second dynamically optimized load module 9 are physically identical and are shown in the schematic diagram. Figure 4 Similarly, the first current-optimized load module 6 and the second current-optimized load module 8 are physically identical in design and are shown in [the diagram]. Figure 5 In the diagram. (The diagram is in...) Figure 4 and 5 The diagram shows the circuits of the corresponding load modules 6, 7, 8, and 9 on the left, a simplified circuit of the corresponding load modules 6, 7, 8, and 9 shown on the left in the middle, and the circuits of the corresponding load modules 6, 7, 8, and 9 shown on the left and in the middle on the right. Figures 1 to 3 The symbols used.

[0046] As by Figure 4 As can be seen, the first dynamically optimized load module 7 and the second dynamically optimized load module 9 are designed as at least three-stage inverters 12, that is, a seven-stage inverter in this case. Thus, the first dynamically optimized load module 7 and the second dynamically optimized load module 9 can achieve an effective switching frequency or bandwidth of 800kHz under a maximum current of 75A. Therefore, due to... Figure 5 As can be seen, the first current-optimized load module 6 and the second current-optimized load module 8 are designed as a two-stage inverter 11, which provides 1000A of current respectively.

[0047] The device also has a control mechanism 10, which, in any case, relates to... Figure 1 The design shown is configured as follows: a second current-optimized load module 8 based on the low-pass filter output voltage control of inverter 1, and a second dynamically optimized load module 9 based on the high-pass filter output voltage control of inverter 1. The control mechanism 10 is computer-based and / or has an FPGA.

[0048] Because inverter 1 and also in Figure 3 The converter 2 shown is a three-phase ground configuration, so in Figures 1 to 3 In the design scheme shown, the second simulation mechanism 4 includes corresponding parallel circuits for each phase of the second dynamically optimized load module 9 and the second current-optimized load module 8. Accordingly, the control mechanism 10 is designed to be based on the inverter 1 or related to... Figure 3 The output voltage of the corresponding phase of inverter 2 is controlled by the low-pass filter of the corresponding phase, which optimizes the second current of the corresponding phase and is based on inverter 1 or related to load module 8. Figure 3 The high-pass filtered output voltage of the corresponding phase of the converter 2 controls the second dynamically optimized load module 9 of the corresponding phase.

[0049] Regarding Figure 1 In the design scheme shown, the control mechanism 10 can also be configured as a load module 6 that controls the first current optimization based on the input current of the inverter 1. This external... Figure 2 As shown, the first simulation mechanism 3, according to this design scheme, has two parallel circuits: a first current-optimized load module 6 and a first dynamic-optimized load module 7. The control mechanism 10, in this design scheme, is configured to control the first current-optimized load module 6 based on the low-pass filtered input current of the inverter 1 and to control the first dynamic-optimized load module 7 based on the high-pass filtered input current of the inverter 1.

[0050] As mentioned above, in Figure 3 The design shown includes a converter 2. A first simulation mechanism 3 includes corresponding parallel circuits for each phase of a first dynamically optimized load module 7 and a first current-optimized load module 6. The control mechanism 10 is accordingly designed to control the first current-optimized load module 6 of the corresponding phase based on the low-pass filter input voltage of the corresponding phase of the converter 2, and to control the first dynamically optimized load module 7 of the corresponding phase based on the high-pass filter input voltage of the corresponding phase of the converter 2. The low-pass filter operates at a cutoff frequency of ≤5kHz, particularly ≤3kHz, and the high-pass filter operates at a cutoff frequency of ≥8kHz, particularly ≥10kHz.

[0051] Regarding Figures 1 to 3 The specific design scheme shown in the figure measures the output voltage U_U_ of inverter 1 or converter 2.Mess U_V Mess U_W Mess and the motor model supplied to the control mechanism 10. The motor model calculates the motor phase target currents is u, is v, is w from the voltages measured on the inverter 1 or the converter 2, wherein the sinusoidal motor current fundamental is u fundamental , is v fundamental , is w fundamental (0 to 5 kHz maximum) and the triangular current ripple of the switching frequency is u rippel , is v rippel , is w rippel (10 kHz to 100 kHz) is superimposed.

[0052] The amplitudes of the motor current fundamental are set by the current regulators of the inverter 1 or the converter 2 as pulse-like power electronics, respectively. The amplitudes of the triangular current ripple of the switching frequency are produced by the motor inductances parameterized in the motor model in combination with the input voltage UDC_Link of the inverter 1 or the converter 2. In order to keep the ripple torque in the traction drive in an admissible range, the drive system is usually designed such that the amplitude of the current ripple does not exceed 10% of the amplitude of the current fundamental.

[0053] In order to greatly increase the power density, a combination of high-current E-load modules that are optimally dimensioned for the motor current fundamental is u fundamental , is v fundamental , is w fundamental (0 to 5 kHz maximum) - which are optimized for high currents, are bandwidth-limited and are characterized by a small cost - namely the first current-optimized load module 6 and the second current-optimized load module 8 - and load modules for the triangular current ripple of the switching frequency is u rippel , is v rippel , is w rippel (10 kHz to 100 kHz) that are designed for the highest dynamics, namely the first dynamic-optimized load module 7 and the second dynamic-optimized load module 9 is selected. In order to depict the current fundamental, a significantly simplified hardware structure is employed, so that a great saving in terms of installation space and cost is possible.

[0054] The motor current target values is u, is v, is w from the motor model are frequency-selectively filtered and split into is u fundamental , is v fundamental , is w fundamental (0 to 5 kHz maximum) and is u rippel , is v rippelis w rippel (10 kHz to 100 kHz). The simplified high-current E-load module achieves the fundamental target value is u fundamental is v fundamental is w fundamental and the dynamically designed load module achieves the ripple target value is u rippel is v rippel is w rippel as target value. The current is u fundamental is v fundamental is w fundamental and is u rippel is v fundamental is w fundamental are superimposed.

[0055] Possible design examples are as follows:

[0056] The fictitious norm high-current E-load module, i.e. the first current-optimized load module 6 and the second current-optimized load module 8:

[0057] I RMS_High_Power_Modul = 300 A, f 3db = 8 kHz

[0058] The norm for high-dynamic E-load module, i.e. the first dynamic-optimized load module 7 and the second dynamic-optimized load module 9:

[0059] I RMS = 75 A, f 3db = 800 kHz

[0060] The system requires motor current simulation:

[0061] Iu,v,w RMS_fundamental = 1000 A => Iu,v,w peak_fundamental = 1414 A

[0062] Assuming a current ripple for the simulation of Iu,v,w peak_fundamental = 1414 A: Iu,v,w peak_rippel = 0.1 * 1414 A = 141.4 A

[0063] To cover the motor fundamental including the current ripple, the following combination can be chosen:

[0064] 3 * high-current E-load module per motor phase, i.e. the first current-optimized load module 6 and the second current-optimized load module 8

[0065] => Iu,v,w RMS_fundamental= 900 A => Iu,v,w Peak_fundamental = 900 A * sqrt(2) = 1272.79 A

[0066] 3 * dynamic E load modules, i.e. for the first dynamic optimized load module 7 and the second dynamic optimized load module 9, per motor phase:

[0067] => Iu,v,w RMS_Rippel = 225 A => Iu,v,w Peak_Rippel = 225 A * sqrt(2) = 318.98 A

[0068] => Iu,v,w RMS = Iu,v,w RMS_fundamental + Iu,v,w RMS_Rippel = 900 A + 225 A = 1125 A / Iu,v,w Peak = Iu,v,w Peak_fundamental + Iu,v,w Peak_Rippel = 1272.79 A + 318.98 A = 1591.77 A

[0069] In contrast, a prior art design example:

[0070] System requires motor current simulation: Iu,v,w RMS_fundamental = 1000 A => Iu,v,w peak_fundamental = 1414 A

[0071] N Module = Iu,v,w Peak_fundamental / I Peak = 1414 A / (75 A * sqrt(2)) = 13.33

[0072] 14 * E load modules are required per motor phase, which is significantly more costly.

[0073] The embodiments are merely examples which can be modified and / or supplemented in various ways within the scope of the claims. Each feature described for a particular embodiment can be used independently of other features or in combination with other features for any one of the other embodiments. Each feature described for a particular type of embodiment can also be used in a corresponding manner for another type of embodiment.

[0074] List of reference signs

[0075] 1 inverter

[0076] 2 current converter

[0077] 3 first simulation mechanism

[0078] 4 second simulation mechanism

[0079] 5. Intermediate circuit capacitors

[0080] 6. Load module with optimized first current

[0081] 7. First Dynamically Optimized Load Module

[0082] 8. Load module with second current optimization

[0083] 9. Second Dynamically Optimized Load Module

[0084] 10 control mechanisms

[0085] 11. Inverters with at least two stages

[0086] 12. Inverters with at least three stages

Claims

1. Device for testing an inverter (1) and / or a converter (2), having a first simulation mechanism (3) which is designed to simulate an energy generator, a second simulation mechanism (4) which is designed to simulate an energy consumer, an inverter (1) and / or a converter (2) which is connected between the first simulation mechanism (3) and the second simulation mechanism (4), the inverter and / or the converter comprising a parallel connection of an intermediate circuit capacitor (5), and a control mechanism (10), wherein the first simulation mechanism (3) comprises at least one first current-optimized load module (6) and the second simulation mechanism (4) comprises at least one parallel circuit of a second dynamic-optimized load module (9) and a second current-optimized load module (8), the first current-optimized load module (6) and the second current-optimized load module (8) each comprise at least two stages of an inverter (11), and the second dynamic-optimized load module (9) comprises at least three stages of an inverter (12), and the control mechanism (10) is designed to control the second current-optimized load module (8) on the basis of a low-pass filtered output voltage of the inverter (1) and / or the converter (2) and to control the second dynamic-optimized load module (9) on the basis of a high-pass filtered output voltage of the inverter (1) and / or the converter (2). The inverter (1) and / or the converter (2) is designed three- phase, the second simulation mechanism (4) comprises for each phase a corresponding parallel circuit of the second dynamic-optimized load module (9) and the second current-optimized load module (8), and the control mechanism (10) is designed to control the second current-optimized load module (8) of a corresponding phase on the basis of a low-pass filtered output voltage of the corresponding phase of the inverter (1) and / or the converter (2) and to control the second dynamic-optimized load module (9) of the corresponding phase on the basis of a high-pass filtered output voltage of the corresponding phase of the inverter (1) and / or the converter (2). The control mechanism (10) is designed to control the first current-optimized load module (6) on the basis of an input current of the inverter (1). The first simulation mechanism (3) comprises at least one, in particular two, parallel circuits of a first current-optimized load module (6) and a first dynamic-optimized load module (7), and the control mechanism (10) is designed to control the first current-optimized load module (6) on the basis of a low-pass filtered input current of the inverter (1) and to control the first dynamic-optimized load module (7) on the basis of a high-pass filtered input current of the inverter (1).

2. The device of the preceding claim, wherein, ​ 3. The device according to any of the preceding claims, comprising an inverter (1), wherein, ​ 4. The device of any of the preceding claims, wherein, ​ 5. The device according to any of the preceding claims, comprising a current transformer (2), wherein, The converter (2) is three-phase, the first simulation mechanism (3) comprises for each phase a respective parallel circuit of a first dynamically optimized load module (7) and a first current-optimized load module (6), and the control mechanism (10) is designed to control the first current-optimized load module (6) of a respective phase of the converter (2) on the basis of a low-pass filtered input voltage of the respective phase and to control the first dynamically optimized load module (7) of the respective phase of the converter (2) on the basis of a high-pass filtered input voltage of the respective phase.

6. The device of any of the preceding claims, wherein, The low-pass filtering is implemented with a cut-off frequency of ≤ 5 kHz, in particular ≤ 3 kHz, and the high-pass filtering is implemented with a cut-off frequency of ≥ 8 kHz, in particular ≥ 10 kHz.

7. The device according to any one of the preceding claims, comprising a plurality of first current-optimized load modules (6) and / or second current-optimized load modules (8) connected in series.

8. The device of any of the preceding claims, wherein, The control mechanism (10) comprises an FPGA.

9. The device of any of the preceding claims, wherein, The first dynamically optimized load module (7) and the second dynamically optimized load module (9) each comprise an inverter (1) of at least seven stages.

10. The device of any of the preceding claims, wherein, The first simulation mechanism (3) comprises a battery and / or a generator, and / or the second simulation mechanism (4) comprises an electric motor and / or a power supply network.

11. Use of a device according to any one of the preceding claims for testing inverters (1) and / or converters (2) of wind power plants, power supply networks and / or batteries, in particular of electric vehicles.

12. Method for testing an inverter (1) and / or a converter (2), with a first simulation mechanism (3) set up to simulate an energy generator, a second simulation mechanism (4) set up to simulate an energy consumer, and an inverter (1) and / or a converter (2) connected between the first simulation mechanism (3) and the second simulation mechanism (4), the inverter and / or the converter comprising a parallel connection of an intermediate circuit capacitor (5), wherein the first simulation mechanism (3) comprises at least one first current-optimized load module (6) and the second simulation mechanism (4) comprises at least one parallel circuit of a second dynamically optimized load module (9) and a second current-optimized load module (8), the first current-optimized load module (6) and the second current-optimized load module (8) each comprise an inverter (11) of at least two stages, and the second dynamically optimized load module (9) comprises an inverter (12) of at least three stages, and comprising the following steps: controlling the second current-optimized load module (8) on the basis of a low-pass filtered output voltage of the inverter (1) and / or the converter (2) and controlling the second dynamically optimized load module (9) on the basis of a high-pass filtered output voltage of the inverter (1) and / or the converter (2).

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